Method and apparatus for transmitting and receiving downlink channel and signal integrated with sensing

Abstract

A method and apparatus for transmitting and receiving a downlink channel and signal integrated with sensing are disclosed. A method of a base station for transmitting and receiving a downlink channel and signal integrated with sensing comprises: generating control information for a sensing-integrated downlink channel and signal based on terminal capability information received from a terminal; generating and transmitting the sensing-integrated downlink channel and signal to the terminal based on the control information; receiving a reflected sensing-integrated downlink channel and signal for the sensing-integrated downlink channel and signal from the terminal; and determining a round-trip delay for the sensing-integrated downlink channel and signal based on the reflected sensing-integrated downlink channel and signal.

Description

Technology Field

[0001] The present disclosure relates to signal transmission technology for a communication network, and more specifically, to a downlink channel integrated with sensing and a method and apparatus for transmitting and receiving signals. Background Technology

[0002] Along with the advancement of information and communication technology, various wireless communication technologies are being developed. Representative wireless communication technologies include LTE (long term evolution) and NR (new radio), which are defined in the 3GPP (3rd generation partnership project) standards. LTE can be one of the wireless communication technologies among 4G (4th Generation) wireless communication technologies, and NR can be one of the wireless communication technologies among 5G (5th Generation) wireless communication technologies.

[0003] To handle the surge in wireless data following the commercialization of 4G communication systems (e.g., communication systems supporting LTE), 5G communication systems (e.g., communication systems supporting NR) that use frequency bands higher than those of 4G communication systems (e.g., frequency bands below 6 GHz) are being considered. 5G communication systems can support eMBB (enhanced Mobile BroadBand), URLLC (Ultra-Reliable and Low Latency Communication), and mMTC (massive Machine Type Communication).

[0004] In communication systems, the Round Trip Time (RTT) method is used to estimate the round-trip delay between a base station and a terminal. In the RTT method, the terminal can receive the base station's downlink reference signal or synchronization signal and estimate the downlink reception timing. In the RTT method, the base station can receive the uplink reference signal from the terminal, estimate the uplink reception timing, and estimate the round-trip delay.

[0005] In the RTT method of a communication system, transmission and reception timing errors between the base station and the terminal may occur, which can lead to errors in round-trip delay estimation. Since the accuracy of round-trip delay estimation varies depending on the performance of the terminal, estimation errors may also occur.

[0006] The round-trip delay estimation error may be inversely proportional to the frequency bandwidth allocated to the reference signal or synchronization signal. To improve the accuracy of round-trip delay estimation, a wide frequency bandwidth may be required for signals transmitted and received between the base station and the terminal, such as downlink or uplink signals.

[0007] As a result, communication systems may face limitations in analog beamforming or multi-user scheduling in high-frequency bands. Since terminals must transmit and receive signals with base stations across a wide frequency band to estimate round-trip delay, this can lead to increased power consumption. Therefore, measures to improve the accuracy of round-trip delay estimation are required. The problem to be solved

[0008] The objective of the present disclosure to address the above-mentioned requirements is to provide a downlink channel integrated with sensing and a method and apparatus for transmitting and receiving signals that can increase the accuracy of round-trip delay estimation with limited bandwidth. means of solving the problem

[0009] A method of a base station for transmitting and receiving a downlink channel and a signal integrated with sensing according to an embodiment of the present disclosure for achieving the above objective may include: generating control information for the sensing-integrated downlink channel and the signal; generating the sensing-integrated downlink channel and the signal based on the control information and transmitting it to the terminal; receiving a reflected sensing-integrated downlink channel and signal for the sensing-integrated downlink channel and the signal from the terminal; and determining a round-trip delay for the sensing-integrated downlink channel and the signal based on the reflected sensing-integrated downlink channel and the signal.

[0010] The method of the base station may further include the step of receiving terminal capability information from the terminal. The step of generating the control information may include: generating a chirp filtering sequence based on a combination of a plurality of parameters; and generating the combination of the plurality of parameters and the chirp filtering sequence as the control information.

[0011] The step of generating the chirp filtering sequence may include generating one of a linear up-down chirp filtering sequence, a linear down-up chirp filtering sequence, an exponential chirp filtering sequence, and a hyperbolic chirp filtering sequence based on a combination of the plurality of parameters.

[0012] The step of generating the chirp filtering sequence may include: generating a frequency shift value for the frequency shift modulation of the terminal based on the terminal capability information; resetting the value of each of the plurality of parameters based on the frequency shift value to generate a new parameter combination; and generating the chirp filtering sequence based on the new parameter combination.

[0013] The above control information may include a time-domain chirp filtering sequence generated based on a combination of multiple parameters. The step of generating the sensing-integrated downlink channel and signal and transmitting it to the terminal may include: converting the time-domain chirp filtering sequence into a frequency-domain chirp filtering sequence; obtaining a transmit modulation symbol based on the frequency-domain chirp filtering sequence; and converting the transmit modulation symbol into an RF signal and transmitting it to the sensing-integrated downlink channel and signal.

[0014] The step of determining the round-trip delay may include: a step of obtaining a frequency domain signal by converting the reflected sensing-integrated downlink channel and signal; a step of obtaining a received modulation symbol by de-mapping the effective bandwidth of the frequency domain signal; a step of obtaining an equalized received modulation symbol by equalizing the received modulation symbol; a step of obtaining a beat signal from the equalized received modulation symbol; and a step of determining the round-trip delay by obtaining at least one of an estimated beat frequency, an estimated distance, or an estimated resolution from the beat signal.

[0015] The step of acquiring the bit signal may include: a step of acquiring a time domain equalized received modulation symbol by converting the equalized received modulation symbol; a step of acquiring a time domain bit signal from the time domain equalized received modulation symbol; and a step of acquiring a frequency domain bit signal by converting the time domain bit signal.

[0016] The step of determining the round-trip delay may include: obtaining a frequency domain bit signal from the reflected sensing-integrated downlink channel and signal; converting the frequency domain bit signal to obtain a time domain bit signal; obtaining a downsampled bit signal from the time domain bit signal based on a preset decimation factor; obtaining a padding bit signal from the downsampled bit signal; and determining the round-trip delay from the padding bit signal based on the decimation factor.

[0017] The step of acquiring the time domain bit signal may include the step of phase-rotating the frequency domain bit signal and converting the phase-rotated frequency domain bit signal to acquire the time domain bit signal.

[0018] The step of acquiring the padding bit signal may include: a step of summing downsampling bit signals having different decimation points using co-phasing; a step of zero-padding the summed downsampling bit signals to acquire a time domain padding bit signal; and a step of converting the time domain padding bit signal to acquire a frequency domain padding bit signal.

[0019] A method of a terminal for transmitting and receiving a downlink channel and a signal integrated with sensing according to an embodiment of the present disclosure for achieving the above objective may include: receiving a sensing-integrated downlink channel and a signal from a base station; reflecting the sensing-integrated downlink channel and the signal to the base station; estimating an effective channel from the sensing-integrated downlink channel and the signal; and decoding the sensing-integrated downlink channel and the signal based on the estimated effective channel.

[0020] The step of estimating the effective channel may include: a step of obtaining a frequency domain signal by converting the sensing-integrated downlink channel and signal; a step of obtaining a received modulation symbol by demapping the frequency domain signal; a step of obtaining an equalized received modulation symbol by equalizing the received modulation symbol; and a step of estimating the effective channel from the equalized received modulation symbol.

[0021] A base station for transmitting and receiving signals and a downlink channel integrated with sensing according to one embodiment of the present disclosure for achieving the above objective may include at least one processor.

[0022] The above at least one processor may cause the base station to generate control information for a sensing-integrated downlink channel and signal, generate the sensing-integrated downlink channel and signal based on the control information and transmit it to the terminal, receive a reflected sensing-integrated downlink channel and signal for the sensing-integrated downlink channel and signal from the terminal, and determine a round-trip delay for the sensing-integrated downlink channel and signal based on the reflected sensing-integrated downlink channel and signal.

[0023] The above at least one processor may cause the base station to receive terminal capability information from the terminal, generate one chirp filtering sequence among a linear up-down chirp filtering sequence, a linear down-up chirp filtering sequence, an exponential chirp filtering sequence, and a hyperbolic chirp filtering sequence based on a combination of a plurality of parameters, and to generate the combination of the plurality of parameters and the one chirp filtering sequence as control information.

[0024] The above at least one processor may further cause the base station to generate a frequency shift value for frequency shift modulation of the terminal based on the terminal capability information, reset the value of each of the plurality of parameters based on the frequency shift value to generate a new parameter combination, and generate the one chirp filtering sequence based on the new parameter combination.

[0025] The above control information may include a time domain chirp filtering sequence generated based on a combination of multiple parameters. The at least one processor may cause the base station to convert the time domain chirp filtering sequence into a frequency domain chirp filtering sequence, acquire a transmit modulation symbol based on the frequency domain chirp filtering sequence, and convert the transmit modulation symbol into an RF signal and transmit it to the sensing-integrated downlink channel and signal.

[0026] The above at least one processor may cause the base station to convert the reflected sensing-integrated downlink channel and signal to obtain a frequency domain signal, de-mapping the effective bandwidth of the frequency domain signal to obtain a received modulation symbol, equalizing the received modulation symbol to obtain an equalized received modulation symbol, obtaining a bit signal from the equalized received modulation symbol, and obtaining at least one of an estimated bit frequency, an estimated distance, or an estimated resolution from the bit signal to determine the round-trip delay.

[0027] The above at least one processor may cause the base station to convert the equalization reception modulation symbol to obtain a time domain equalization reception modulation symbol, obtain a time domain bit signal from the time domain equalization reception modulation symbol, and convert the time domain bit signal to obtain a frequency domain bit signal.

[0028] The at least one processor above may cause the base station to acquire a frequency domain bit signal from the reflected sensing-integrated downlink channel and signal, phase-rotate the frequency domain bit signal, convert the phase-rotated frequency domain bit signal to acquire a time domain bit signal, acquire a downsampled bit signal from the time domain bit signal based on a preset decimation factor, acquire a padding bit signal from the downsampled bit signal, and determine the round-trip delay from the padding bit signal based on the decimation factor.

[0029] The above at least one processor may cause the base station to sum downsampling bit signals having different decimation points in co-phasing, zero-padding the summed downsampling bit signals to obtain a time domain padding bit signal, and convert the time domain padding bit signal to obtain a frequency domain padding bit signal. Effects of the invention

[0030] According to the present disclosure, a base station can perform downlink communication and round-trip delay determination on the same time and frequency resources from the sensing-integrated-integrated downlink channel and signal transmitted to the terminal. Accordingly, the base station can improve the performance of round-trip delay determination in a limited bandwidth and can obtain a sophisticated power delay profile (PDP) for multipath, thereby obtaining a channel for a high-resolution delay area. In addition, the base station can perform round-trip delay determination along with downlink communication, thereby preventing scheduling constraints for multiple users and improving the accuracy of round-trip delay determination in a limited bandwidth, which can reduce the battery consumption of the terminal. Brief explanation of the drawing

[0031] Figure 1 is a conceptual diagram showing an example of a communication network. FIG. 2 is a block diagram showing an example of a communication node of a communication network. FIG. 3 is a flowchart illustrating an example of a method for transmitting a sensing-integrated downlink channel and signals between a base station and a terminal in a communication network. FIG. 4 is a flowchart illustrating an example of a method for determining round-trip delay in a base station in a reflected sensing-integrated downlink channel and signal. FIG. 5 is a flowchart illustrating an example of a method for improving the determination performance of round-trip delay in a reflected sensing-integrated downlink channel and signal of a base station. FIG. 6 is a flowchart illustrating an example of a method for a terminal to decode a sensing-integrated downlink channel and a signal. Specific details for implementing the invention

[0032] The present disclosure is capable of various modifications and may have various embodiments, and specific embodiments are illustrated in the drawings and described in detail. However, this is not intended to limit the present disclosure to specific embodiments, and it should be understood that it includes all modifications, equivalents, and substitutions that fall within the spirit and scope of the present disclosure.

[0033] Terms such as "first," "second," etc., may be used to describe various components, but said components should not be limited by said terms. Such terms are used solely for the purpose of distinguishing one component from another. For example, without departing from the scope of the present disclosure, the first component may be named the second component, and similarly, the second component may be named the first component. The term "and / or" includes a combination of a plurality of related described items or any of a plurality of related described items.

[0034] When it is stated that one component is "connected" or "connected" to another component, it should be understood that while it may be directly connected or connected to that other component, there may also be other components in between. On the other hand, when it is stated that one component is "directly connected" or "directly connected" to another component, it should be understood that there are no other components in between.

[0035] The terms used in this disclosure are used merely to describe specific embodiments and are not intended to limit this disclosure. The singular expression includes the plural expression unless the context clearly indicates otherwise. In this disclosure, terms such as “comprising” or “having” are intended to specify the existence of the features, numbers, steps, actions, components, parts, or combinations thereof described in the specification, and should be understood as not precluding the existence or addition of one or more other features, numbers, steps, actions, components, parts, or combinations thereof.

[0036] Unless otherwise defined, all terms used herein, including technical or scientific terms, have the same meaning as generally understood by those skilled in the art to which this disclosure pertains. Terms such as those defined in commonly used dictionaries should be interpreted as having a meaning consistent with their meaning in the context of the relevant technology, and should not be interpreted in an ideal or overly formal sense unless explicitly defined in this disclosure.

[0037] A communication network to which embodiments according to the present disclosure are applied will be described. The communication network may be a non-terrestrial network (NTN), a 4G communication network (e.g., a long-term evolution (LTE) communication network), a 5G communication network (e.g., a new radio (NR) communication network), a B5G mobile communication network (e.g., a 6G mobile communication network), etc. 4G communication networks and 5G communication networks may be classified as terrestrial networks.

[0038] In an embodiment, "an operation (e.g., a transmission operation) being set in a communication node" may mean that "setting information for said operation (e.g., an information element, a parameter)" and / or "information directing the execution of said operation" is signaled to said communication node. In other words, "an operation (e.g., a transmission operation) being set in a communication node" may mean that said communication node receives "setting information for said operation (e.g., an information element, a parameter)" and / or "information directing the execution of said operation." "An information element (e.g., a parameter) being set in a communication node" may mean that said information element is signaled to said communication node (e.g., said communication node receiving said information element). The signaling may be at least one of SI (system information) signaling (e.g., transmission of SIB (system information block) and / or MIB (master information block)), RRC signaling (e.g., transmission of RRC parameters and / or upper layer parameters), MAC CE (control element) signaling, or PHY signaling (e.g., transmission of DCI (downlink control information), UCI (uplink control information), and / or SCI (sidelink control information).

[0039] In the present disclosure, even when a method performed at a first communication node among the communication nodes (e.g., transmission or reception of a signal) is described, the corresponding second communication node may perform a method corresponding to the method performed at the first communication node (e.g., reception or transmission of a signal). For example, when the operation of a terminal is described, the base station corresponding to the terminal may perform an operation corresponding to the operation of the terminal. Conversely, when the operation of a base station is described, the terminal corresponding to the base station may perform an operation corresponding to the operation of the base station. Furthermore, when the operation of a first terminal is described, the second terminal corresponding to the first terminal may perform an operation corresponding to the operation of the first terminal. Conversely, when the operation of a second terminal is described, the first terminal corresponding to the second terminal may perform an operation corresponding to the operation of the second terminal.

[0040] Throughout the specification, the term "terminal" may refer to a mobile station, mobile terminal, subscriber station, portable subscriber station, user equipment, access terminal, etc., and may include all or part of the functions of a terminal, mobile station, mobile terminal, subscriber station, portable subscriber station, user equipment, access terminal, etc.

[0041] Here, a desktop computer, laptop computer, tablet PC, wireless phone, mobile phone, smartphone, smart watch, smart glass, e-book reader, PMP (portable multimedia player), portable game console, navigation device, digital camera, DMB (digital multimedia broadcasting) player, digital audio recorder, digital audio player, digital picture recorder, digital picture player, digital video recorder, digital video player, etc., capable of communicating with a terminal can be used.

[0042] Throughout the specification, the term "base station" may refer to an access point, a radio access station, a node B, an evolved node B, a base transceiver station, a mobile multihop relay (MMR)-BS, etc., and may include all or part of the functions of a base station, access point, radio access station, node B, eNodeB, base transceiver station, MMR-BS, etc.

[0043] Hereinafter, preferred embodiments of the present disclosure will be described in more detail with reference to the attached drawings. In order to facilitate an overall understanding of the present disclosure, the same reference numerals are used for identical components in the drawings, and redundant descriptions of identical components are omitted.

[0044] Figure 1 is a conceptual diagram showing an example of a communication network.

[0045] Referring to FIG. 1, the communication network (100) may include a plurality of communication nodes (110-1, 110-2, 110-3, 120-1, 120-2, 130-1, 130-2, 130-3, 130-4, 130-5, 130-6). A plurality of communication nodes (110-1, 110-2, 110-3, 120-1, 120-2, 130-1, 130-2, 130-3, 130-4, 130-5, 130-6) may include a plurality of base stations (110-1, 110-2, 110-3, 120-1, 120-2) and a plurality of terminals, such as a plurality of user terminals (130-1, 130-2, 130-3, 130-4, 130-5, 130-6).

[0046] Each of the multiple communication nodes (110-1, 110-2, 110-3, 120-1, 120-2, 130-1, 130-2, 130-3, 130-4, 130-5, 130-6) can support 4G communication (e.g., LTE (long term evolution), LTE-A (advanced)), 5G communication (e.g., NR (new radio)), etc., as defined in the 3GPP (3rd generation partnership project) standard. 4G communication can be performed in a frequency band of 6 GHz or lower, and 5G communication can be performed not only in a frequency band of 6 GHz or lower but also in a frequency band of 6 GHz or higher.

[0047] For example, for 4G communication and 5G communication, each of the multiple communication nodes (110-1, 110-2, 110-3, 120-1, 120-2, 130-1, 130-2, 130-3, 130-4, 130-5, 130-6) has a CDMA (code division multiple access) based communication protocol, a WCDMA (wideband CDMA) based communication protocol, a TDMA (time division multiple access) based communication protocol, a FDMA (frequency division multiple access) based communication protocol, an OFDM (orthogonal frequency division multiplexing) based communication protocol, a Filtered OFDM based communication protocol, a CP (cyclic prefix)-OFDM based communication protocol, a DFT-s-OFDM (discrete Fourier transform-spread-OFDM) based communication protocol, an OFDMA (orthogonal frequency division multiple access) based communication protocol, a SC (single carrier)-FDMA based communication protocol, It can support communication protocols based on NOMA (Non-orthogonal Multiple Access), GFDM (generalized frequency division multiplexing), FBMC (filter bank multi-carrier) and UFMC (universal filtered multi-carrier) and SDMA (Space Division Multiple Access).

[0048] Additionally, although not illustrated in the drawing, the communication network (100) may further include a core network. If the communication network (100) supports 4G communication, the core network may include an S-GW (serving-gateway), a P-GW (PDN (packet data network)-gateway), an MME (mobility management entity), etc. If the communication network (100) supports 5G communication, the core network may include a UPF (user plane function), an SMF (session management function), an AMF (access and mobility management function), etc.

[0049] FIG. 2 is a block diagram showing an example of a communication node of a communication network.

[0050] Referring to FIG. 2, the communication node (200) may include at least one processor (210), a memory (220), and a transceiver (230) that is connected to a network to perform communication. Additionally, the communication node (200) may further include an input interface device (240), an output interface device (250), a storage device (260), etc. Each component included in the communication node (200) may be connected by a bus (270) to communicate with one another.

[0051] However, each component included in the communication node (200) may be connected via individual interfaces or individual buses centered around the processor (210), rather than via a common bus (270). For example, the processor (210) may be connected via a dedicated interface to at least one of a memory (220), a transmission / reception device (230), an input interface device (240), an output interface device (250), and a storage device (260).

[0052] The processor (210) can execute a program command stored in at least one of the memory (220) and the storage device (260). The processor (210) may mean a central processing unit (CPU), a graphics processing unit (GPU), or a dedicated processor on which the methods according to the embodiments of the present disclosure are performed.

[0053] Each of the memory (220) and the storage device (260) may be composed of at least one of a volatile storage medium and a non-volatile storage medium. For example, the memory (220) may be composed of at least one of a read-only memory (ROM) and a random access memory (RAM).

[0054] FIG. 3 is a flowchart illustrating an example of a method for transmitting a sensing-integrated downlink channel and signals between a base station and a terminal in a communication network.

[0055] The base station (310) shown in FIG. 3 may be one of a plurality of base stations (110-1, 110-2, 110-3, 120-1, 120-2) constituting the communication network of FIG. 1. The terminal (330) shown in FIG. 3 may be one of a plurality of user terminals (130-1, 130-2, 130-3, 130-4, 130-5, 130-6) constituting the communication network of FIG. 1.

[0056] In the present disclosure, a base station (310) may transmit a sensing-integrated downlink channel and a signal to a terminal (330). The sensing-integrated downlink channel and the signal may be a sensing-integrated downlink channel and a signal for estimating the round-trip delay of signal transmission and reception between the base station (310) and the terminal (330). The sensing-integrated downlink channel and the sensing-integrated downlink signal may be mapped to resources that are orthogonal to each other in terms of time and frequency resources.

[0057] The sensing-integrated downlink channel may include at least one of a data or message modulation symbol filtered into a chirp (compressed high intensity radar pulse) sequence. The data or message modulation symbol may be a symbol that modulates the data or message sequence transmitted to the physical layer through an upper layer.

[0058] The sensing-integrated downlink signal may include at least one of the modulation symbols of a reference signal or a synchronization signal filtered by a chirp sequence. The reference signal may include at least one of a channel state information reference signal (CSI-RS), a demodulation reference signal (DMRS), or a phase tracking reference signal (PT-RS). The synchronization signal may include at least one of a primary synchronization signal (PSS) or a secondary synchronization signal (SSS). The reference signal modulation symbol may be a symbol that modulates the reference signal sequence, and the synchronization signal modulation symbol may be a symbol that modulates the synchronization signal sequence.

[0059] Referring to FIG. 3, the terminal (330) can report terminal capability information (UE capability information) to the base station (310) (S310). For example, the terminal (330) may include a radio frequency (RF) chip that reflects a received channel and signal by frequency shift keying (FSK). The terminal can FSK modulate the received channel and signal with a single or multiple frequency shift values ​​through the RF chip. Accordingly, the terminal can report terminal capability information to the base station (310) that includes at least one of information regarding whether FSK modulation is possible through the RF chip, the modulationable frequency band, and the entire set or a subset of frequency shift values. The terminal (330) can report capability information necessary for transmitting and receiving downlink channels and signals integrated with sensing to the base station (310).

[0060] The base station (310) can receive terminal capability information and, based thereon, generate control information related to the sensing-integrated downlink channel and signal and transmit it to the terminal (330) (S320). The control information may include at least one of control information related to the downlink channel and control information related to the downlink signal.

[0061] Downlink channel related control information may include at least one of an indicator capable of indicating that the channel is a sensing-integrated downlink channel, a combination of multiple parameters, a chirp filtering sequence generated according to the combination of multiple parameters, whether the terminal is FSK modulated based on terminal capability information, a frequency shift value or whether the terminal is back-reflected array operating, an extended CP (Cyclic Prefix) length setting value, and a parameter for channel decoding. Downlink channel related control information may be indexed into a look-up table (LUT).

[0062] Control information related to downlink signals may include an indicator that indicates that the signal is a sensing-integrated downlink signal, whether the terminal is FSK modulating based on terminal capability information, a frequency shift value or whether the terminal is back-reflecting array operating, an extended CP length setting value, and at least one of the relevant parameters required for the terminal (330) to estimate the channel or synchronization based on the assigned signal.

[0063] In the present disclosure, the sensing-integrated downlink channel and signal transmitted from the base station (310) to the terminal (330) may be a channel and signal filtered by a chirp sequence, that is, a chirp filtering sequence. The chirp filtering sequence may include at least one of a linear chirp filtering sequence, an exponential chirp filtering sequence, or a hyperbolic chirp filtering sequence.

[0064] Among the chirp filtering sequences, the linear chirp filtering sequence may be a sequence in which a continuous-time linear chirp filtering signal is sampled into N time-domain samples that are equally spaced over the time-domain length. The continuous-time linear chirp filtering signal can be defined as [Equation 1] below. The base station (310) can generate a linear chirp filtering sequence as [Equation 2] below.

[0065]

[0066] Here, can be a square pulse, c0, c1 and c2 can be parameter values, and T can be a time domain length.

[0067]

[0068] Here, c0, c1, and c2 can be parameter values, T can be the time domain length, and N can be the number of time domain samples.

[0069] The base station (310) can generate various types of linear chirp filtering sequences depending on the combination of parameters (c0, c1, c2). For example, the base station (310) can generate a linear up-down chirp filtering sequence having an effective bandwidth for the sampling frequency based on a combination of parameters (c0, c1, c2) such as [Equation 3] below for any phase.

[0070]

[0071] Here, can be any phase, T can be the length of the time domain, and N can be the number of time domain samples.

[0072] As another example, the base station (310) can generate a linear down-up chirp filtering sequence having an effective bandwidth for the sampling frequency based on a combination of parameters (c0, c1, c2) as shown in [Equation 4] below for any phase.

[0073]

[0074] Here, can be any phase, T can be the length of the time domain, and N can be the number of time domain samples.

[0075] As another example, the base station (310) can generate a linear chirp filtering sequence with an effective bandwidth centered on a direct current (DC) subcarrier based on a combination of parameters (c0, c1, c2) as shown in [Equation 5] below for any phase.

[0076]

[0077] Here, can be any phase, T can be the length of the time domain, and B can be the effective bandwidth for the sampling frequency.

[0078] The base station (310) can generate an exponential chirp filtering sequence for a continuous-time linear chirp filtering signal as shown in [Equation 6] below. The exponential chirp filtering sequence can be generated in various forms depending on the combination of parameters (c0, c1, c2).

[0079]

[0080] Here, c0 and c2 can be parameter values, T can be the time domain length, N can be the number of time domain samples, and ln can be an exponential logarithmic function.

[0081] The base station (310) can generate a hyperbolic chirp filtering sequence for a continuous-time linear chirp filtering signal as shown in [Equation 7] below. The hyperbolic chirp filtering sequence can be generated in various forms depending on the combination of parameters (c0, c1, c2).

[0082]

[0083] Here, c0, c1 and c2 can be parameter values, T can be the time domain length, N can be the number of time domain samples, and ln can be an exponential logarithmic function.

[0084] The base station (310) can generate various combinations of parameters (c0, c1, c2) of the aforementioned chirp filtering sequence and transmit them to the terminal (330) as sensing-integrated downlink channel and signal-related control information. The base station (310) can index each parameter (c0, c1, c2) or a combination thereof into a lookup table and transmit it.

[0085] For example, the base station (310) can generate a predefined fixed parameter combination from the parameters (c0, c1, c2). The base station (310) can generate a parameter combination by setting some of the parameters (c0, c1, c2) as fixed parameters and the rest as parameters corresponding to the frequency domain. The base station (310) may also generate different parameter combinations in sets of one or more OFDM (orthogonal frequency division multiplexing) symbols for the time domain to which the integrated downlink channel is allocated.

[0086] Based on the received terminal capability information, the base station (310) can transmit the FSK modulation status or frequency shift value of the terminal (330) to the terminal (330) as sensing-integrated downlink channel and signal-related control information. At this time, the base station (310) can generate a new parameter combination by resetting at least one parameter value among the parameters (c0, c1, c2) based on the frequency shift value as shown in [Equation 8] below. Based on the new parameter combination, the base station (310) can generate the aforementioned chirp filtering sequence, for example, a linear chirp filtering sequence, an exponential chirp filtering sequence, or a hyperbolic chirp filtering sequence.

[0087]

[0088] Here, c1 can be a parameter value and f0 can be a frequency shift value.

[0089] The chirp filtering sequence generated at the base station (310) may be a time domain sequence. The base station (310) can obtain a frequency domain chirp filtering sequence as shown in [Equation 9] below by performing a discrete Fourier transform (DFT) on the time domain chirp filtering sequence of [Equation 2].

[0090]

[0091] Here, N can be the number of time-domain samples, and It can be a time-domain chirp filtering sequence.

[0092] The base station (310) can obtain a frequency domain chirp filtering sequence as shown in [Equation 10] below by performing a discrete Fourier transform on a linear up-down chirp filtering sequence according to the parameter combination of [Equation 3].

[0093]

[0094] Here, can be any phase, and N can be the number of time domain samples.

[0095] The base station (310) can generate combinations of frequency domain parameters (c0, c1, c2) as shown in [Equation 11] below for the frequency domain chirp filtering sequence of [Equation 10].

[0096]

[0097] Here, can be any phase, and N can be the number of time domain samples.

[0098] The base station (310) can obtain a frequency domain chirp filtering sequence as shown in [Equation 12] below by performing a discrete Fourier transform on a linear down-up chirp filtering sequence according to the parameter combination of [Equation 4].

[0099]

[0100] Here, can be any phase, and N can be the number of time domain samples.

[0101] The base station (310) can generate combinations of frequency domain parameters (c0, c1, c2) as shown in [Equation 13] below for the frequency domain chirp filtering sequence of [Equation 12].

[0102]

[0103] Here, can be any phase, and N can be the number of time domain samples.

[0104] The base station (310) can generate a chirp-filtered transmission modulation symbol for the k-th subcarrier in the frequency domain as shown in [Equation 14] below by multiplying the modulation symbol of the sensing-integrated downlink channel and signal by a frequency domain chirp filtering sequence. The modulation symbol of the sensing-integrated downlink channel and signal may be a data / message modulation symbol of the integrated downlink channel, a reference signal modulation symbol of the integrated downlink signal, or a synchronization signal modulation symbol of the integrated downlink signal.

[0105]

[0106] Here, Φ[k] may be a frequency domain chirp filtering sequence, X[k] may be a modulation symbol of the sensing-integrated downlink channel and signal, and N may be the number of time domain samples.

[0107] The base station (310) can map the transmitted modulation symbol to the entire subcarrier assigned to the integrated downlink channel or signal. The base station (310) can obtain the transmitted modulation symbol in the time domain as shown in [Equation 15] below by performing an inverse discrete Fourier transform (IDFT) on the transmitted modulation symbol.

[0108]

[0109] Here, S[k] can be a transmitted modulation symbol, and N can be the number of time-domain samples.

[0110] Time domain transmission modulation symbols may have characteristics according to [Equation 16] below.

[0111]

[0112] Here, can be a discrete circular convolution operator.

[0113] The base station (310) can map the transmitted modulation symbol to some subcarriers assigned to the integrated downlink channel or signal. For example, the base station (310) can map the transmitted modulation symbol to the effective bandwidth for the sampling frequency of the linear chirp filtering sequence within the bandwidth of the integrated downlink channel or signal. At this time, the base station (310) can null the subcarriers to which the transmitted modulation symbol is not mapped, and can obtain the transmitted modulation symbol in the time domain as shown in [Equation 17] below by performing an inverse discrete Fourier transform on the transmitted modulation symbol.

[0114]

[0115] Here, can be a transmitted modulation symbol, and N can be the number of time domain samples.

[0116] In [Equation 17], when Ns is equal to N, the sampling frequency can be equal to the effective bandwidth (or effective frequency band). As a result, the time domain transmission modulation symbol according to [Equation 17] can be equal to the time domain transmission modulation symbol according to [Equation 15].

[0117] The base station (310) can convert the time domain transmission modulation symbol into an RF signal by digital-to-analog conversion (DAC), frequency conversion, power amplification, analog filtering, or analog beamforming. The base station (310) can transmit the converted RF signal to the terminal (330) as a sensing-integrated downlink channel and signal (S330).

[0118] The terminal (330) can receive a sensing-integrated downlink channel and signal from the base station (310). The terminal (330) can estimate the received integrated downlink channel and can decode the sensing-integrated downlink channel and signal based on the estimated channel (S340).

[0119] Meanwhile, the terminal (330) can reflect the received sensing-integrated downlink channel and signal by frequency shift modulation. The base station (310) can receive the sensing-integrated downlink channel and signal reflected from the terminal (330) (S350).

[0120] The base station (310) can receive the sensing-integrated downlink channel and signal reflected from the terminal (330), and can determine the round-trip delay for the previously transmitted sensing-integrated downlink channel and signal based on the reflected sensing-integrated downlink channel and signal (S360).

[0121] FIG. 4 is a flowchart illustrating an example of a method for determining round-trip delay in a base station in a reflected sensing-integrated downlink channel and signal.

[0122] Referring to FIG. 4, the base station (310) can receive a sensing-integrated downlink channel and signal reflected from the terminal (330). The base station (310) can frequency convert the reflected sensing-integrated downlink channel and signal (S410).

[0123] The reflected sensing-integrated downlink channel and signal can be a round-trip received signal and can be defined as [Equation 18] below.

[0124]

[0125] Here, α can be the path attenuation of the round-trip channel, β can be the path attenuation of the self-interference channel, and P t ε can be the transmission power, h[n] can be the nth round-trip channel tap, and ψ can be the self-interference channel coefficient, and can be a transmitted modulation symbol, N can be the number of time-domain samples, and w r [n] can be additive white Gaussian noise (AWGN).

[0126] The round-trip channel and the self-interference channel may be baseband effective channels including effects such as the transmitting and receiving analog or digital beamforming of the base station (310), analog or digital filtering, and the reflection array coefficient of the terminal (330). The base station (310) may remove self-interference components through the transmitting and receiving analog or digital beamforming, analog or digital filtering, etc.

[0127] The reflected sensing-integrated downlink channel and signal may be a round-trip received signal in the time domain. The base station (310) may perform self-interference suppression filtering on the reflected sensing-integrated downlink channel and signal, and may obtain a signal in the frequency domain by performing frequency conversion, e.g., a discrete Fourier transform.

[0128] The base station (310) can de-mapping the frequency-converted signal and can obtain the received modulation symbol (S420).

[0129] The base station (310) can perform demapping on the effective bandwidth of the converted signal. The base station (310) can obtain the demapping signal, that is, the received modulation symbol, according to the demapping as shown in [Equation 19] below.

[0130]

[0131] Here, α can be the path attenuation of the round-trip channel, and P t can be the transmission power, S[k] can be the transmitted modulation symbol, and H[k] can be the frequency domain round-trip channel coefficient of the k-th subcarrier, and can be noise corresponding to the k-th subcarrier.

[0132] The base station (310) can equalize the received modulated symbols and obtain the equalized received modulated symbols (S430).

[0133] The base station (310) can perform zero-forcing (ZF) equalization by dividing the received modulation symbol into the sensing-integrated downlink channel and the modulation symbol of the signal. The base station (310) can obtain the equalized received modulation symbol as shown in [Equation 20] below, depending on the equalization of the received modulation symbol.

[0134]

[0135] Here, can be a received modulation symbol, X[k] can be a modulation symbol of the sensing-integrated downlink channel and signal, α can be the path attenuation of the round-trip channel, and P t ≡ can be transmission power, H[k] can be the frequency domain round-trip channel coefficient of the k-th subcarrier, and Z[k] can be noise.

[0136] The base station (310) can obtain the equalized received modulation symbol in the time domain as shown in [Equation 21] below by performing an inverse discrete Fourier transform on the equalized received modulation symbol.

[0137]

[0138] Here, α can be the path attenuation of the round-trip channel, and P t can be the transmission power, and h[n] can be the nth round-trip channel tap, and can be a time-domain chirp filtering sequence, and N can be the number of time-domain samples.

[0139] The base station (310) can obtain a time domain beat signal from the time domain equalization received modulation symbol as shown in [Equation 22] below (S440).

[0140]

[0141] Here, * can be a complex conjugate operator, α can be the path attenuation of a round-trip channel, Pt can be the transmission power, L0 can be the minimum index of a non-zero channel tap, and L can be the number of non-zero channel taps, and silver It could be the th round-trip channel tap, can be a time-domain chirp filtering sequence, Z[n] can be noise, and N can be the number of time-domain samples.

[0142] The base station (310) can substitute a linear down-up chirp filtering sequence according to the parameter combination of the aforementioned [Equation 4] into the time domain chirp filtering sequence of [Equation 22]. The base station (310) can acquire a time domain bit signal as shown in [Equation 23] below.

[0143]

[0144] Here, * can be the complex conjugate operator, α can be the path attenuation of the round-trip channel, and P t can be the transmission power, L0 can be the minimum index of a non-zero channel tap, and L can be the number of non-zero channel taps, and silver It could be the th round-trip channel tap, can be noise, and N can be the number of time domain samples.

[0145] The base station (310) can convert the time domain bit signal into the frequency domain bit signal and determine the round-trip delay for the sensing-integrated downlink channel and signal based on the converted bit signal (S450).

[0146] The base station (310) can obtain a frequency domain bit signal by performing a discrete Fourier transform on the time domain bit signal as shown in [Equation 24] below.

[0147]

[0148] Here, * can be the complex conjugate operator, α can be the path attenuation of the round-trip channel, and P t ε₀ may be the transmission power, h[k] may be the k-th round-trip channel tap, Z[k] may be noise, N may be the number of time domain samples, L0 may be the minimum index of a non-zero channel tap, and L may be the number of non-zero channel taps.

[0149] A single line of sight (LoS) path can be configured between the base station (310) and the terminal (330). Based on the single LoS path, the k-th round-trip channel tap of the baseband channel can be modeled as shown in [Equation 25] below.

[0150]

[0151] Here, sinc can be a sink function, and f r It can be a beat frequency.

[0152] Also, beat frequency f r is f s τ / T can be 2R / c, R can be the LoS path distance between the base station and the terminal, and c can be the speed of light.

[0153] The base station (310) can obtain an estimated bit frequency from the frequency domain bit signal based on [Equation 25] as shown in [Equation 26] below.

[0154]

[0155] Here, B[k] can be a frequency domain bit signal and T can be a time domain length.

[0156] The base station (310) can obtain an estimated distance based on the estimated beat frequency as shown in [Equation 27] below.

[0157]

[0158] Here, c can be the speed of light, and f r It can be the beat frequency.

[0159] The base station (310) can obtain an estimated resolution based on the obtained estimated distance as shown in [Equation 28] below.

[0160]

[0161] Here, c can be the speed of light and f can be the subcarrier interval.

[0162] As described above, the reflected sensing-integrated downlink channel and signal received by the base station (310) may be a round-trip received signal for the downlink transmission of the base station (310). The base station (310) may determine a round-trip delay for the downlink channel and signal transmission of the base station (310) based on at least one of the bit frequency, distance, or resolution estimated from the reflected sensing-integrated downlink channel and signal.

[0163] For example, the base station (310) can obtain an estimated round-trip delay as shown in [Equation 29] below, based on the estimated beat frequency obtained according to [Equation 26].

[0164]

[0165] Here, can be the estimated beat frequency, and c can be the speed of light.

[0166] FIG. 5 is a flowchart illustrating an example of a method for improving the performance of round-trip delay determination in a base station's reflected sensing-integrated downlink channel and signal.

[0167] Referring to FIG. 5, the base station (310) can acquire a sensing-integrated downlink channel and signal reflected from the terminal (330), and can acquire a frequency domain bit signal from the reflected sensing-integrated downlink channel and signal. The base station (310) can convert the frequency domain bit signal to acquire a time domain bit signal (S510).

[0168] The base station (310) can perform self-interference suppression filtering on the reflected sensing-integrated downlink channel and signal, and can obtain a signal in the frequency domain by performing a discrete Fourier transform. The base station (310) can obtain a received modulation symbol through demapping the effective bandwidth of the transformed signal, and can obtain an equalized received modulation symbol by equalizing the received modulation symbol. The base station (310) can obtain an equalized received modulation symbol in the time domain by performing an inverse discrete Fourier transform on the equalized received modulation symbol, and can obtain a time domain bit signal from the time domain equalized received modulation symbol. The base station (310) can obtain a frequency domain bit signal by performing a discrete Fourier transform on the time domain bit signal.

[0169] The base station (310) can phase-rotate the frequency domain bit signal and obtain a phase-rotated signal with respect to the subcarrier as shown in [Equation 30] below. The base station (310) can obtain a time domain bit signal by performing an inverse discrete Fourier transform on the phase-rotated frequency domain bit signal.

[0170]

[0171] Here, B[k] can be a frequency domain bit signal.

[0172] The base station (310) can decimate the time domain bit signal based on a preset factor, for example, a decimation factor. The base station (310) can obtain downsampled bit signals for a plurality of different decimation points as shown in [Equation 31] below (S520).

[0173]

[0174] Here, can be a time domain bit signal, D can be a decimation factor, and d can be a decimation point.

[0175] The base station (310) can set a decimation factor by considering at least one of the distance from the terminal (330), the inter-site distance (ISD), the CP length, the transmission power, or the timing advance (TA).

[0176] Based on the estimated bit frequency obtained, the base station (310) can sum downsampling bit signals having different decimation points as shown in [Equation 32] below in co-phasing.

[0177]

[0178] Here, D can be a decimation factor, and d can be a decimation point, and can be an estimated beat frequency.

[0179] The base station (310) can zero-padding the downsampling bit signal and obtain the padding bit signal as shown in [Equation 33] below (S530).

[0180]

[0181] Here, can be a downsampling bit signal, and D can be a decimation factor.

[0182] The base station (310) can obtain a frequency domain padding bit signal by performing a discrete Fourier transform on the padding bit signal as shown in [Equation 34] below.

[0183]

[0184] Here, α can be the path attenuation of the round-trip channel, and P tε can be the transmission power, D can be the decimation factor, N can be the number of time-domain samples, sinc can be the sink function, M can be the ratio of the magnitude of the Discrete Fourier Transform to the number of time-domain samples (N), T can be the time-domain length, and f r It can be the beat frequency, It could be noise.

[0185] The base station (310) can obtain an estimated bit frequency from a padded bit signal in the frequency domain based on a decimation factor as shown in [Equation 35] below. Based on the estimated bit frequency, the base station (310) can obtain an estimated round-trip delay as shown in [Equation 36] below. Based on the estimated round-trip delay, the base station (310) can obtain an estimated distance as shown in [Equation 37] below. Based on the estimated bit frequency or the estimated distance, the base station (310) can determine a round-trip delay for the sensing-integrated downlink channel and signal (S540).

[0186]

[0187] Here, can be a padding bit signal, M can be the ratio of the size of the discrete Fourier transform to the number of time domain samples (N), L can be the number of non-zero channel taps, and T can be the time domain length.

[0188]

[0189] Here, can be the estimated beat frequency, and c can be the speed of light.

[0190]

[0191] Here, can be the estimated round-trip delay, and c can be the speed of light.

[0192] The base station (310) can improve the estimation resolution of the beat frequency or improve the estimation signal-to-noise ratio (SNR) by combining zero padding or oversampling techniques. The accuracy of the beat frequency, round-trip delay, and distance estimation of the base station (310) can be improved.

[0193] FIG. 6 is a flowchart illustrating an example of a method for a terminal to decode a sensing-integrated downlink channel and a signal.

[0194] Referring to FIG. 6, the terminal (330) can receive RF signals, for example, time domain sensing-integrated downlink channel and signals from the base station (310). The terminal (330) can obtain frequency domain signals by performing a discrete Fourier transform on the time domain sensing-integrated downlink channel and signals (S610).

[0195] The sensing-integrated downlink channel and signal received by the terminal (330) can be defined as shown in [Equation 38] below.

[0196]

[0197] Here, can be effective communication channel attenuation, and P t can be the transmission power, and g[n] can be the nth communication channel tap, and can be a transmitted modulation symbol, and w c [n] can be additive white Gaussian noise (AWGN), and N s can be the length of the time domain.

[0198] The effective communication channel may be a baseband effective channel based on the transmitting analog / digital beamforming, analog / digital filtering, or receiving analog / digital beamforming of the base station (310). For example, the base station (310) may suppress self-interference components through transmitting analog / digital beamforming or analog / digital filtering, and may beamform the sensing-integrated downlink channel and signal toward the terminal (330). The terminal (330) may perform beamforming toward the base station (310) through receiving analog / digital beamforming.

[0199] The terminal (330) can obtain a received modulated symbol as shown in [Equation 39] below through demapping of the effective bandwidth of the frequency domain signal (S620).

[0200]

[0201] Here, can be effective communication channel attenuation, and P t can be the transmission power, G[k] can be the communication channel tap for the subcarrier index, X[k] can be the modulation symbol of the sensing-integrated downlink channel and signal, Φ[k] can be the frequency domain chirp filtering sequence, and W c [k] can be noise, N can be the time domain length, and k can be the subcarrier index.

[0202] The terminal (330) can equalize the received modulation symbol to obtain an equalized received modulation symbol as shown in [Equation 40] below (S630). The terminal (330) can perform zero-forcing (ZF) equalization.

[0203]

[0204] Here, Y[k] can be a received modulation symbol, and can be effective communication channel attenuation, and P tcan be the transmission power, G[k] can be the communication channel tap for the subcarrier index, X[k] can be the modulation symbol of the sensing-integrated downlink channel and signal, and Φ[k] can be the frequency domain chirp filtering sequence, can be effective noise, N can be the time domain length, and k can be the subcarrier index.

[0205] The terminal (330) can estimate an effective channel from the equalized received modulation symbol (S640). The terminal (330) can equalize the channel of the equalized received modulation symbol based on the estimated effective channel (S650). The terminal (330) can decode the data and message modulation symbols of the sensing-integrated downlink channel and signal from the received modulation symbol with the equalized channel (S660).

[0206] The operation of the method according to an embodiment of the present disclosure can be implemented as a computer-readable program or code on a computer-readable recording medium. A computer-readable recording medium includes all types of recording devices in which information that can be read by a computer system is stored. Additionally, the computer-readable recording medium may be distributed across networked computer systems, and the computer-readable program or code may be stored and executed in a distributed manner.

[0207] In addition, computer-readable recording media may include hardware devices specifically configured to store and execute program instructions, such as ROM, RAM, and flash memory. Program instructions may include machine code, such as that generated by a compiler, as well as high-level language code that can be executed by a computer using an interpreter, etc.

[0208] Some aspects of the present disclosure have been described in the context of a device, but may also be described according to a corresponding method, wherein a block or device corresponds to a method step or a feature of a method step. Similarly, aspects described in the context of a method may also be described according to a corresponding block or item or a feature of a corresponding device. Some or all of the method steps may be performed by (or using) a hardware device, such as, for example, a microprocessor, a programmable computer, or an electronic circuit. In some embodiments, at least one of the most important method steps may be performed by such a device.

[0209] In the embodiments, a programmable logic device (e.g., a field-programmable gate array) may be used to perform some or all of the functions of the methods described herein. In the embodiments, a field-programmable gate array may operate with a microprocessor to perform one of the methods described herein. Generally, it is preferable that the methods be performed by some hardware device.

[0210] Although the present disclosure has been described with reference to preferred embodiments, those skilled in the art will understand that various modifications and changes can be made to the present disclosure without departing from the spirit and scope of the present disclosure as set forth in the following claims.

Claims

Claim 1 A method of a base station comprising: generating a time-domain chirp filtering sequence based on a combination of a plurality of parameters based on terminal capability information; generating control information for a sensing-integrated downlink channel and a signal based on the combination of the plurality of parameters and the time-domain chirp filtering sequence; generating the sensing-integrated downlink channel and a signal based on the control information and transmitting it to the terminal; receiving a reflected signal for the sensing-integrated downlink channel and a signal from the terminal; and determining a round-trip delay for the sensing-integrated downlink channel and a signal based on the reflected signal, wherein the sensing-integrated downlink signal includes at least one modulation symbol among a downlink reference signal and a synchronization signal filtered by the chirp filtering sequence, and the sensing-integrated downlink channel includes at least one modulation symbol among data and a message filtered by the chirp filtering sequence. Claim 2 delete Claim 3 A method of a base station according to claim 1, wherein the step of generating the time domain chirp filtering sequence comprises generating one of the time domain chirp filtering sequences, a linear up-down chirp filtering sequence, a linear down-up chirp filtering sequence, an exponential chirp filtering sequence, and a hyperbolic chirp filtering sequence based on a combination of the plurality of parameters. Claim 4 A method of a base station according to claim 1, wherein the step of generating the time domain chirp filtering sequence comprises: generating a frequency shift value for frequency shift modulation of the terminal based on the terminal capability information; resetting the value of each of the plurality of parameters based on the frequency shift value to generate a new parameter combination; and generating the time domain chirp filtering sequence based on the new parameter combination. Claim 5 A method of a base station according to claim 1, wherein the step of generating the sensing-integrated downlink channel and signal and transmitting it to the terminal comprises: converting the time domain chirp filtering sequence into a frequency domain chirp filtering sequence; obtaining a transmit modulation symbol based on the frequency domain chirp filtering sequence; and converting the transmit modulation symbol into an RF signal and transmitting it to the terminal as the sensing-integrated downlink channel and signal. Claim 6 A method of a base station according to claim 1, wherein the step of determining the round-trip delay comprises: a step of converting the reflected signal to obtain a frequency domain signal; a step of de-mapping the effective bandwidth of the frequency domain signal to obtain a received modulation symbol; a step of equalizing the received modulation symbol to obtain an equalized received modulation symbol; a step of obtaining a beat signal from the equalized received modulation symbol; and a step of obtaining at least one of an estimated beat frequency, an estimated distance, or an estimated resolution from the beat signal to determine the round-trip delay. Claim 7 A method of a base station according to claim 6, wherein the step of acquiring the bit signal comprises: a step of acquiring a time domain equalized received modulation symbol by converting the equalized received modulation symbol; a step of acquiring a time domain bit signal from the time domain equalized received modulation symbol; and a step of acquiring a frequency domain bit signal by converting the time domain bit signal. Claim 8 A method of a base station according to claim 1, wherein the step of determining the round-trip delay comprises: obtaining a frequency domain bit signal from the reflected signal; converting the frequency domain bit signal to obtain a time domain bit signal; obtaining a downsampled bit signal from the time domain bit signal based on a preset decimation factor; obtaining a padding bit signal from the downsampled bit signal; and determining the round-trip delay from the padding bit signal based on the decimation factor. Claim 9 A method of a base station according to claim 8, wherein the step of acquiring the time domain bit signal comprises the step of phase-rotating the frequency domain bit signal and converting the phase-rotated frequency domain bit signal to acquire the time domain bit signal. Claim 10 A method of a base station according to claim 8, wherein the step of acquiring the padding bit signal comprises: a step of summing downsampling bit signals having different decimation points in co-phasing; a step of zero-padding the summed downsampling bit signals to acquire a time domain padding bit signal; and a step of converting the time domain padding bit signal to acquire a frequency domain padding bit signal. Claim 11 delete Claim 12 delete Claim 13 A base station comprising at least one processor, wherein the at least one processor causes the base station to generate a time-domain chirp filtering sequence based on a combination of a plurality of parameters based on terminal capability information, generate control information for a sensing-integrated downlink channel and signal based on the combination of the plurality of parameters and the time-domain chirp filtering sequence, generate the sensing-integrated downlink channel and signal based on the control information and transmit it to the terminal, receive a reflected signal for the sensing-integrated downlink channel and signal from the terminal, and cause the base station to determine a round-trip delay for the sensing-integrated downlink channel and signal based on the reflected signal, wherein the sensing-integrated downlink signal includes at least one modulation symbol among a downlink reference signal and a synchronization signal filtered by the chirp filtering sequence, and the sensing-integrated downlink channel includes at least one modulation symbol among data and messages filtered by the chirp filtering sequence. Claim 14 In claim 13, the at least one processor causes the base station to generate one of the time domain chirp filtering sequences, a linear up-down chirp filtering sequence, an exponential chirp filtering sequence, and a hyperbolic chirp filtering sequence based on a combination of the plurality of parameters, and to generate the combination of the plurality of parameters and the time domain chirp filtering sequence as control information. Claim 15 In claim 14, the at least one processor further causes the base station to generate a frequency shift value for frequency shift modulation of the terminal based on the terminal capability information, reset the value of each of the plurality of parameters based on the frequency shift value to generate a new parameter combination, and generate the time domain chirp filtering sequence based on the new parameter combination. Claim 16 In claim 13, the at least one processor causes the base station to convert the time domain chirp filtering sequence into a frequency domain chirp filtering sequence, acquire a transmit modulation symbol based on the frequency domain chirp filtering sequence, and convert the transmit modulation symbol into an RF signal to transmit to the terminal via the sensing-integrated downlink channel and signal. Claim 17 In claim 13, the at least one processor causes the base station to convert the reflected signal to obtain a frequency domain signal, de-mapping the effective bandwidth of the frequency domain signal to obtain a received modulation symbol, equalizing the received modulation symbol to obtain an equalized received modulation symbol, obtaining a bit signal from the equalized received modulation symbol, and obtaining at least one of an estimated bit frequency, an estimated distance, or an estimated resolution from the bit signal to determine the round-trip delay. Claim 18 In claim 17, the at least one processor causes the base station to convert the equalization received modulation symbol to obtain a time domain equalization received modulation symbol, obtain a time domain bit signal from the time domain equalization received modulation symbol, and convert the time domain bit signal to obtain a frequency domain bit signal. Claim 19 In claim 13, the at least one processor causes the base station to acquire a frequency domain bit signal from the reflected signal, phase-rotate the frequency domain bit signal, convert the phase-rotated frequency domain bit signal to acquire a time domain bit signal, acquire a downsampled bit signal from the time domain bit signal based on a preset decimation factor, acquire a padding bit signal from the downsampled bit signal, and determine the round-trip delay from the padding bit signal based on the decimation factor. Claim 20 In claim 19, the at least one processor causes the base station to sum downsampling bit signals having different decimation points in co-phasing, zero-padding the summed downsampling bit signals to obtain a time domain padding bit signal, and convert the time domain padding bit signal to obtain a frequency domain padding bit signal.

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