Power converter with integrated bidirectional start-up

Abstract

Circuits and methods including power converters that can be started and operated in a reverse unidirectional manner or a bidirectional manner while providing sufficient voltage for associated auxiliary circuits and start-up without the addition of external circuits for voltage boosters and / or pre-charge circuits - i.e., zero or a reduced number of external components. Embodiments include auxiliary circuits configured to selectively couple to the greater of a first voltage or a second voltage from a power converter to provide power to the auxiliary circuit. Embodiments include auxiliary circuits configured to selectively couple a sub-circuit to the greater of a first voltage or a second voltage from a power converter to provide an output for the auxiliary circuit. Embodiments include charge pumps including a gate driver configured to selectively couple to one of a first voltage node or a second voltage node of the charge pump.

Description

[0001] Cross-references to related applications

[0002] This application claims priority to U.S. Patent Application No. 16 / 749,844, filed January 22, 2020, the contents of which are incorporated herein by reference in their entirety. Technical Field

[0003] This invention relates to electronic circuits, and more particularly to power converter circuits, including DC-DC power converter circuits. Background Technology

[0004] Many electronic products, especially mobile computing and / or communication products and components (e.g., laptops, ultrabooks, tablets, LCD and LED displays), require multiple voltage levels. For example, radio frequency (RF) transmitter power amplifiers may require relatively high voltages (e.g., 12 V or higher), while logic circuit systems may require lower voltage levels (e.g., 1 V to 2 V). Other circuit systems may require intermediate voltage levels (e.g., 5 V to 10 V).

[0005] Power converters are typically used to generate lower or higher voltages from a common power source such as a battery. Power converters include DC-DC or AC-DC converters. One type of power converter includes converter circuitry, control circuitry, and auxiliary circuitry, such as bias voltage generators, clock generators, voltage regulators, and voltage control circuits. Power converters that generate a lower output voltage level from a higher input voltage source are often called buck converters, named so because of the voltage drop across the input source. OUT Less than V IN Therefore, the converter "steps down" the input voltage. A power converter that generates a higher output voltage level from a lower input voltage source is often called a boost converter because V... OUT Greater than V IN .

[0006] Figure 1A This is a block diagram of a prior art unidirectional power converter 100. The converter circuit 102, having input terminals T1 / T1' and output terminals T2 / T2', is configured such that input terminal T1 / T1' is coupled to a voltage source 104 (e.g., a battery), and output terminal T2 / T2' is coupled to an output capacitor C. OUTand load 106. The converter circuit 102 can be, for example, a switched capacitor network such as a charge pump, or an inductor-based regulator. Examples of charge pumps include cascaded multipliers, Dickson, ladder, series-parallel, Fibonacci, and Doubler switched capacitor networks, all of which can be configured as multiphase or single-phase switched capacitor networks. The power converter 100 based on the charge pump-type converter circuit 102 uses capacitors as the primary energy storage elements to transfer charge from the input to the output of the power converter 100. These charge transfer capacitors are commonly referred to as "flycapacitors" or "pump capacitors" and can be external components coupled to the integrated circuit implementation of the power converter 100. In contrast, the power converter 100 using an inductor-based regulator for the converter circuit 102 uses inductors or transformers, rather than capacitors, as the primary energy storage elements. Examples of inductor-based regulators include well-known buck, boost, buck-boost, resonant, multistage, Cook (Cuk), SEPIC, forward, and full-bridge configurations.

[0007] In the example shown, the voltage applied to the input terminals T1 / T1' is V. IN And the conversion voltage provided at the output terminals T2 / T2' is V OUT The controller 108 outputs a set of control signals 112, which control the internal components of the converter circuit 102 (e.g., internal switches such as low-voltage FETs, especially MOSFETs) to cause the converter circuit 102 to switch V... IN Boost or buck to V OUT The controller 108 can also receive a separate set of control signals 112 instructing the converter circuit 102 to operate. The auxiliary circuit 110 can handle various voltages and / or signals, such as voltage V. DD Clock signal CLK, circuit bias voltage V BIAS And one or more control signals CTRL are provided to controller 108 (and optionally directly to converter circuit 102). In V INPUT Power is supplied to the auxiliary circuit 110 shown. (It should be noted that although this disclosure distinguishes between power converter 100 and converter circuit 102, many documents refer to the entire power converter 100 as "power converter" or the converter circuit 102 as "charge pump".)

[0008] Many buck converters and boost converters are designed to be unidirectional, in which most or all components of the converter circuit 102, controller 108, and auxiliary circuit 110 are integrated within a single integrated circuit or circuit module. Therefore, by design, the circuit system for a unidirectional power converter is derived from its input voltage V. IN Power supply, because voltage source 104 (e.g., battery) can be used at the input to provide power to the circuit system. For example, as Figure 1A As shown, the auxiliary circuit 110 is supplied with voltage V by voltage source 104. IN Power supply, the voltage source 104 is coupled to the V of the auxiliary circuit 110. INPUT Terminals (and input terminal T1 of converter circuit 102).

[0009] Figure 1B It is shown that it is used for Figure 1A A block diagram of an example auxiliary circuit 110 of the power converter 100. Voltage V from voltage source 104. IN Coupled to V INPUT And it is applied to voltage regulator 122, which generates a regulated output voltage V. DD (For example, 1.8 V, 3.3 V, or 4.5 V). Unless V IN Exceeding the expected minimum value V MIN Otherwise, the undervoltage lockout (UVLO) circuit 124 is also coupled to V. INPUT And prevent the operation of voltage regulator 122 (and thus prevent V) DD (output). The UVLO circuit 124 can also adjust the output based on voltage V. IN Less than V MIN Or at least V MIN The control signal CTRL is provided to controller 108 to disable or enable the operation of controller 108. V from voltage regulator 122 DD The output can be coupled to bias generator 126 and oscillator 128. Bias generator 126 will bias voltage V. BIAS The oscillator 128 outputs one or more clock signals CLK (e.g., single-phase timing pulses, or two or more timing pulse phases) to controller 108 (and optionally directly to converter circuit 102). Typically, low-voltage FETs (especially MOSFETs) will be used in most or all of the sub-circuits within auxiliary circuitry 110. In a variant, if some voltages and / or signals (e.g., V...) are... DD V BIASIf CLK is available, some of the voltages and / or signals can be provided from outside the system (thus eliminating some components of the auxiliary circuit 110), but doing so reduces the self-sufficiency and independence of the power converter 100, which is contrary to the industrial trend of electronic circuit systems toward higher integration.

[0010] Sometimes, it can be useful to utilize an existing unidirectional power converter in a reverse configuration, making V IN and V OUT The voltage is switched relative to the nominal input terminals T1 / T1' and output terminals T2 / T2' of converter circuit 102. Therefore, for example, it may be useful to change a circuit designed as a unidirectional buck power converter to a boost power converter, and it may also be useful to change a circuit designed as a boost power converter to a unidirectional buck power converter, thereby expanding the application range of a single circuit design.

[0011] Furthermore, unidirectional power converters are not well-suited for all applications. For example, many electronic applications may require rechargeable battery power, configured so that power sometimes flows from the battery to the load, and at other times flows in the opposite direction to charge the battery. Such applications can include, for example, laptops and electric vehicles with two separate batteries. In the example of an electric vehicle, the internal combustion engine and / or regenerative braking can provide recharged power to the battery, which is then used to power the electric drive system. Such applications typically require bidirectional power converters, which can be dynamically configured as buck or boost converters with operating modes selectable by the control circuitry. Therefore, sometimes, the voltage V IN and V OUT The application is effectively switched at the input and output terminals of converter circuit 102. (Note that the type of power converter considered here inherently supports bidirectional power flow once it is operating in steady state; it is the initial enable and startup that define the unidirectional nature of such a power converter.)

[0012] The problem with power converters operating in a "reverse" configuration or mode is that the converter circuit 102, combined with the control circuit system, depends on the input voltage V applied to the valid input terminal. IN And generate output voltage V OUT Previously, in the effective V OUT There is insufficient voltage at the terminals. For example, Figure 2A It shows Figure 1A A block diagram 200 of the reverse operation configuration of the unidirectional power converter 100, wherein... Figure 1A Compared to the voltage source 104 and load 106 shown, voltage source 104' and load 106' are swapped. Therefore, converter circuit 102 is configured such that terminal T1 / T1' is coupled to output capacitor C.OUT And load 106', and terminals T2 / T2' are coupled to voltage source 104', and marked V OUT and V IN and Figure 1A Conversely, therefore, V coupled to auxiliary circuit 110 INPUT The voltage is V OUT Because V INPUT It is also coupled to input terminal T1 of converter circuit 102. Figure 2A In the configuration shown, the voltage V OUT The voltage may be zero or too low to power the auxiliary circuit 110 before the converter circuit 102 can operate, because the auxiliary circuit 110 does not have enough voltage to make the controller 108 operate—a cycle-start problem. Only when V... OUT Reaching or exceeding the specified minimum voltage V MIN Only then will the auxiliary circuit 110 become operable and enable the operation of the converter circuit 102.

[0013] The existing solution to the startup problem is to create a separate voltage supply that provides a voltage greater than the minimum voltage V. MIN The necessary voltage is used to power the auxiliary circuit 110, regardless of the direction of power conversion; that is, the V from the converter circuit 102. OUT and V IN None of these are directly used to power auxiliary circuit 110. This solution increases system complexity by requiring a suitable voltage to exist or be added for this purpose. If such a voltage is not yet available, additional circuitry is needed to power the circuit according to V. IN This voltage is generated, potentially requiring the addition of another auxiliary power converter solely to enable the main power converter 200. If the power converter 200 operates as a buck converter, the voltage V from voltage source 104'... IN Higher than voltage V OUT Generating a lower voltage from an available higher voltage source is relatively simple—the additional circuitry can take the form of a low-dropout regulator (LDO) or a resistive voltage divider. However, if the power converter 200 operates as a boost converter, the voltage V from the voltage source 104'... IN Below voltage V OUT Generating higher voltages from available lower voltage sources is more difficult—additional circuitry will typically take the form of other power converters, such as switched capacitor networks or inductor-based boost regulators. Inductors are generally much larger in overall size and more expensive than capacitors.

[0014] A solution is taught in co-pending U.S. Patent Application No. 16 / 749,785, filed January 22, 2020, entitled “Reversed-OperationPower Converter Startup Circuit and Method,” which is assigned to the assignee of this invention and the contents of that U.S. Patent Application are incorporated herein by reference. The solution is to provide a voltage booster coupled to V IN With V OUT Between, and configured to apply voltage to V OUT Up to the point where a normal power converter operation provides sufficient V OUT Voltage. For example, Figure 2A A voltage booster 202 is shown, which can be, for example, a charge pump circuit. The voltage booster 202 will typically be implemented as an external circuit coupled to the converter circuit 102. Note that as the conversion rate of the converter circuit 102 increases, the voltage booster 202 will likely also require a higher conversion rate, and the circuit size for the charge pump-based implementation of the voltage booster 202 begins to become comparable to that of an inductor-based boost regulator.

[0015] If converter circuit 102 is primarily a buck power converter, it can be enabled for reverse boost operation (e.g., by providing a separate voltage supply to auxiliary circuit 110, or by including voltage booster 202). Figure 2A As shown, the input voltage V IN Supply to terminals T2, T2'). However, if the converter circuit 102 is primarily a boost power converter, enabling it for reverse buck operation can be simpler because the higher voltage V... IN In the auxiliary circuit 110 V INPUT Generating a lower voltage does not require a voltage booster 202. Instead, the solution includes a pre-charge circuit 204 that generates a voltage lower than the input voltage V. IN One or more voltage levels, and may be coupled to one or more nodes within the converter circuit 102. For example, Figure 2B yes Figure 2A A schematic diagram of one embodiment of the pre-charge circuit 204, which is coupled to one or more nodes within the converter circuit 102 and / or coupled to the V of the auxiliary circuit 110. INPUT In the example shown, a set of resistors R1 to R5, typically with equal values, connected in series, provide a resistor divider to apply voltage V based on the voltage V at the top of the resistor divider. C5 Generating partial voltage V X And optionally generate a partial voltage V C1 To VC4 The top node V of the resistor divider C5 and bottom node V SS The terminals T2 and T2' are respectively coupled to the converter circuit 102, resulting in a voltage V C5 Equal to the input voltage V at terminal T2 IN Voltage V X Terminal T1 can be coupled to converter circuit 102, which is already coupled to auxiliary circuit 110. INPUT In this way, the pre-charge circuit 204 can supply the necessary voltage to be equal to or greater than V. MIN V INPUT In order to enable Figure 2A The controller 108 and converter circuit 102 are included. Once the converter circuit 102 begins operation, Figure 2B Diodes D0 to D4 in the circuit can be used to connect the resistor divider to V. X and V C1 To V C4 Voltage separation at the point. The pre-charge circuit 204 can also be implemented as an external circuit coupled to the converter circuit 102 by replacing diodes D0 to D4 with switches as needed. In this way, the pre-charge circuit 204 can be enabled or disabled as needed to support the reverse buck operation of the unidirectional boost power converter 200.

[0016] The desired outcome is that the converter circuit 102 can be started and operated in a reverse unidirectional or bidirectional manner, while providing sufficient voltage to the associated auxiliary circuit 110, without requiring additional external circuitry such as the voltage booster 202 or the precharge circuit 204—that is, zero external components. This invention meets this requirement and provides additional benefits. Summary of the Invention

[0017] The present invention includes circuitry and methods associated with a power converter that can be started and operated in a reverse unidirectional or bidirectional manner while providing sufficient voltage for associated auxiliary circuitry and startup without the need for external circuitry such as voltage boosters and / or pre-charge circuitry—that is, for some embodiments, there are zero external components, or for other embodiments, there are a reduced number of external components.

[0018] Some implementations include an auxiliary circuit configured to provide various voltages and / or signals to a power converter control circuit system and a power converter having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage. The auxiliary circuit includes at least one input voltage selector configured to be coupled to the first and second terminals of the power converter and configured to selectively couple to the greater of the first or second voltage to supply power to the auxiliary circuit.

[0019] Some implementations include an auxiliary circuit configured to provide various voltages and / or signals to other circuit systems. The auxiliary circuit includes at least a first sub-circuit coupled to a first terminal of a power converter; and at least a second sub-circuit coupled to a second terminal of the power converter. The auxiliary circuit is configured to selectively couple to at least one sub-circuit of a first voltage or a second voltage to provide an output for the auxiliary circuit.

[0020] A significant advantage of this auxiliary circuit implementation is that it enables analog multiplexers and / or sub-circuit selection circuit systems without the need for additional external circuitry such as voltage boost circuits or pre-charge circuits.

[0021] Some implementations include an improved gate driver circuit that includes a level shifter and a gate driver configured to be selectively coupled to either a first output source potential or a second output source potential, and to convert an input switching signal having a first voltage into an output switching signal having a second voltage, wherein the gate driver circuit is configured to control the corresponding transistor switch of the power converter. In an implementation of a power converter in which a charge pump performs the power conversion, the first output source potential originates from a first voltage node of the charge pump, and the second output source potential originates from a different second voltage node of the charge pump.

[0022] A significant benefit of the improved gate driver and associated power converter configuration is that this circuit system can be implemented without the need for additional external circuitry for pre-charging.

[0023] Embodiments of the present invention may include the inventive concepts of both, thereby eliminating the need for an external voltage booster circuit and an external precharge circuit.

[0024] Details of one or more embodiments of the invention are set forth in the accompanying drawings and the following description. Other features, objects, and advantages of the invention will become apparent from the description, the drawings, and the claims. Attached Figure Description

[0025] Figure 1AThis is a block diagram of a unidirectional power converter in the prior art.

[0026] Figure 1B It is shown that it is used for Figure 1A A block diagram of an example auxiliary circuit for a power converter.

[0027] Figure 2A It shows Figure 1A A block diagram of the reverse operation configuration of a unidirectional power converter, wherein... Figure 1A Compared to the voltage source and load shown, the voltage source and load have been swapped.

[0028] Figure 2B yes Figure 2A A schematic diagram of one embodiment of the pre-charge circuit, which is coupled to one or more nodes within the converter circuit and / or coupled to the V of the auxiliary circuit. INPUT .

[0029] Figure 3A This is a block diagram of a first embodiment of the present invention, showing a dual-voltage arrangement of auxiliary circuitry for a converter circuit.

[0030] Figure 3B This is a block diagram of a second embodiment of the present invention, showing a dual-input voltage selector arrangement for an auxiliary circuit of a converter circuit.

[0031] Figure 4A yes Figure 3B A schematic diagram of a first embodiment of a first input voltage selector.

[0032] Figure 4B yes Figure 3B A schematic diagram of a second embodiment of the first input voltage selector.

[0033] Figure 5A yes Figure 3B A schematic diagram of a first variant implementation of the UVLO circuit.

[0034] Figure 5B yes Figure 3B A schematic diagram of a second variant implementation of the UVLO circuit.

[0035] Figure 6A This is a circuit diagram of a prior art converter circuit, which includes a single-phase symmetrical cascaded multiplier with a boost ratio of 1:5, and can be used as... Figure 1A An example of a converter circuit.

[0036] Figure 6B This is a block diagram of a gate driver circuit in the prior art.

[0037] Figure 7A It is possible to be with Figure 6A A block diagram of the converter circuit combined with the improved gate driver circuit.

[0038] Figure 7B This is a circuit diagram of a modified converter circuit, which includes a single-phase symmetrical cascaded multiplier with a boost ratio of 1:5, and can be used as... Figure 1A An example of a converter circuit.

[0039] Figure 8 This is a flowchart illustrating a first method for supplying power to the auxiliary circuitry of a power converter.

[0040] Figure 9 This is a flowchart illustrating a method for selecting among multiple sub-circuits in the auxiliary circuitry of a power converter.

[0041] Figure 10 This is a flowchart illustrating a method for providing power to the gate driver circuit of the corresponding transistor switch of a power converter.

[0042] The same reference numerals in the various figures indicate the same elements. Detailed Implementation

[0043] The present invention includes circuitry and methods associated with a power converter that can be started and operated in a reverse unidirectional or bidirectional manner while providing sufficient voltage for associated auxiliary circuitry and startup without the need for external circuitry such as voltage boosters and / or pre-charge circuitry—that is, for some embodiments, there are zero external components, or for other embodiments, there are a reduced number of external components.

[0044] Selective voltage input to converter auxiliary circuit

[0045] Figure 3A This is a block diagram 300 of a first embodiment of the present invention, illustrating a dual-voltage arrangement of auxiliary circuit 302 for converter circuit 304. Converter circuit 304 can be similar to... Figure 1A and Figure 2A The converter circuit 102, but the voltage marking has been changed to V. A and V B Instead of V IN and V OUT This reflects that the converter circuit 304 can operate in either reverse unidirectional or bidirectional mode. The auxiliary circuit 302 can be similar to... Figure 1A The auxiliary circuit 110 includes an input voltage selector 306, which has separate couplings to V A and V B Input A and B.

[0046] The input voltage selector 306 is used as an analog multiplexer, allowing selection of V. A or V B As the input voltage V to the auxiliary circuit 302 INPUT Inside the auxiliary circuit 302, V from the selected input A or B A or V B The voltage in is used for various sub-circuits such as UVLO circuit 124 and voltage regulator 122 (see Figure 1B Power supply. The input voltage selector 306 can be integrated on the same integrated circuit (IC) die as part of the auxiliary circuit 302, or it can be a separate IC die, for example, in a module that includes the IC die implementation of the auxiliary circuit 302.

[0047] In some implementations, this can be achieved, for example, through the controller 108 (not in Figure 3A The selection signal (or signal shown) actively controls which input, A or B, is used as the input voltage V. INPUT The selection signal depends on which of the two applied voltages V is coupled to. A V B The larger of the two values ​​is used to select input A or input B. Furthermore, the selection can be based on existing knowledge of the forward or reverse configuration of the converter circuit 304, rather than on V. A and V B The relative voltage at the input voltage is determined to control the input voltage selection. For example, such knowledge could come from a mode setting signal from controller 108, or from a trim or memory component within controller 108. In other embodiments, the input voltage selector 306 can automatically select between two applied voltages V. A and V B The larger of the two (see example below).

[0048] Therefore, for example, if converter circuit 304 is used in a buck power converter operating in the forward (buck) direction, then V A The voltage will always be higher, therefore input A of input voltage selector 306 will be selected to power auxiliary circuit 302. However, if the same converter circuit 304 operates in reverse (boost) direction, then V B The voltage will be relatively high until after the converter circuit 304 has started operating, and therefore during the startup phase, input B of the input voltage selector 306 will be selected to power the auxiliary circuit 302, after which input A of the input voltage selector 306 can be selected (or self-selected) to power the auxiliary circuit 302. After startup, during the steady-state operation of the converter circuit 304, the voltage will continue to be high at V. A or V BThe lower of the two voltages is generally more efficient for powering auxiliary circuit 302, provided that the voltage meets or exceeds the specified minimum voltage V. MIN .

[0049] Similarly, if converter circuit 304 is used in a boost power converter operating in the forward (boost) direction, then V A The voltage will be higher until the converter circuit 304 operates, and therefore during the startup phase, input A of the input voltage selector 306 will be selected to power the auxiliary circuit 302, after which input B of the input voltage selector 306 can be selected (or self-selected) to power the auxiliary circuit 302. However, if the same converter circuit 304 operates in the reverse (buck) direction, then V B The voltage will always be relatively high, and therefore input B of input voltage selector 306 will be selected to power auxiliary circuit 302. Similarly, after startup, during the steady-state operation of converter circuit 304, the voltage will continue to be V. A or V B The lower of the two voltages is generally more efficient for powering auxiliary circuit 302, provided that the voltage meets or exceeds the specified minimum voltage V. MIN .

[0050] Figure 3A A single input voltage selector 306 for auxiliary circuit 302 is shown. In an alternative implementation, it is necessary to select V. A or V B Each sub-circuit within the auxiliary circuit 302, which serves as the input voltage, can have its own voltage selector circuit. For example, Figure 3B This is block diagram 320 of a second embodiment of the present invention, illustrating a dual-input voltage selector arrangement for an auxiliary circuit 302 for a converter circuit 304. In the illustrated embodiment, the voltage regulator 122 has a corresponding first input voltage selector 306a, which has a voltage selector coupled to V... A and V B The inputs A and B are given, and the UVLO circuit 124 has a corresponding second input voltage selector 306b, which has a voltage selector 306b coupled to V respectively. A and V B Inputs A and B. One advantage of the illustrated embodiment is that the first input voltage selector 306a and the second input voltage selector 306b can be customized for the circuit characteristics of the voltage regulator 122 and the UVLO circuit 124. The first input voltage selector 306a and the second input voltage selector 306b can be the same circuit (but can have different circuit values), or they can be different circuits, and there are multiple ways to implement either input voltage selector 306a or 306b.

[0051] For example, Figure 4A yes Figure 3B A schematic diagram of a first embodiment 306a1 of the first input voltage selector 306a. The voltage from the converter circuit 304 is... A The voltage is applied to the first diode D1, which is connected in series with the first resistor R1. In parallel, the voltage from the converter circuit 304 is... B The voltage is applied to the second diode D2, which is connected in series with the second resistor R2. Output node V SEL Coupled to resistors R1 and R2 (note that the order of diodes D1 and D2 and the corresponding resistors R1 and R2 can be reversed without affecting operation). Diodes D1 and D2 essentially isolate the voltage of one input from the other. V SEL The output voltage at point V A and V B The maximum value (minus the forward voltage of each diode), and the circuit automatically selects the larger voltage as V. SEL To output. For efficiency reasons, in order to favor one input over others during steady-state operation, the resistor values ​​in the favored path can be designed to be much lower than the resistor values ​​in the unfavored path.

[0052] As another example, Figure 4B yes Figure 3B A schematic diagram of a second embodiment 306a2 of the first input voltage selector 306a. The voltage from the converter circuit 304 is... A The voltage is applied to the first switch S1, which is optionally coupled in parallel with the first diode D1 (which may be an inherent parasitic diode for some switching techniques), and converts the voltage from the converter circuit 304 to the voltage. B The voltage is applied to the second switch S2, which is optionally coupled in parallel with the second diode D2 (again, for some switching techniques, it may be an inherent parasitic diode). Output node V SEL Coupled to two switches S1 and S2. Switches S1 and S2 can be actively controlled, for example, by a selection signal from controller 108. If a V signal is detected from converter circuit 304... A The voltage is higher than that from V B If the voltage is such that the controller 108 closes switch S1 and opens switch S2, the input voltage can be transferred from V... A Pass to V SEL Conversely, if a signal from V is detected... A The voltage is lower than that from V B If the voltage is such that the controller 108 can open switch S1 and close switch S2, the input voltage can be transferred from V... B Pass to V SELAlternatively, the states of switches S1 and S2 can be set by controller 108 based on information about whether converter circuit 304 is operating in the forward or reverse direction.

[0053] If diodes D1 and D2 are optionally or inherently coupled in parallel with the corresponding switches S1 and S2, then the second embodiment 306a2 can be like Figure 4A It operates as in the first embodiment 306a1, and independently selects the input voltage V independently of switches S1 and S2. A and V B The larger one in V SEL Output. By bypassing the diode's forward voltage drop with a much smaller switching voltage drop, turning off the switch coupled to the forward-biased diode allows more of the corresponding input voltage to flow from V. A or V B Pass to V SEL This allows for a more efficient solution while ensuring the V of the auxiliary circuit 302. INPUT The required value is higher than V. MIN A larger voltage margin.

[0054] Figure 4A and Figure 4B Any of the embodiments 306a1 and 306a2 shown can be used as the input voltage selector 306b for the UVLO circuit 124. It should be clear that... Figure 4A and Figure 4B Other variations of the circuit shown, as well as other analog multiplexer circuits, can be used for input voltage selectors 306, 306a, and 306b.

[0055] In other embodiments, the function of the input voltage selector can be more tightly integrated within the circuitry of the voltage regulator 122 and / or UVLO circuit 124. For example, an actively controlled or self-selecting circuitry can enable or disable sub-circuits within the voltage regulator 122 and / or UVLO circuit 124 to effectively select the input voltage selected by the voltage from the converter circuit 304. A or V B One of the power supply sub-circuits.

[0056] For example, Figure 5A yes Figure 3B A schematic diagram of a first variant implementation 124a of the UVLO circuit 124. The V from the converter circuit 304... A The voltage is applied to the first undervoltage lockout circuit UVLO A, while the V from the converter circuit 304 is... BThe voltage is applied to the second undervoltage lockout circuit, UVLO B. An output selector 310, coupled to UVLO A and UVLO B, selects which undervoltage lockout circuit to use, outputting a CTRL signal to other circuits in response to an input selection signal. For example, this can be determined by controller 108 based on a comparison from V... A and from V B The selection signal is generated by the voltage. Alternatively, the controller 108 may generate the selection signal based on information about whether the converter circuit 304 is operating in the forward or reverse direction. In a variant embodiment, if the undervoltage lockout circuits UVLO A and UVLO B can be enabled and disabled separately, the output selector 310 can be omitted, and the undervoltage lockout circuits UVLO A and UVLO B can be directly selected using the selection signal to couple to the CTRL output.

[0057] As another example, Figure 5B yes Figure 3B A schematic diagram of a second variant implementation 124b of the UVLO circuit 124. The V from the converter circuit 304... A The voltage is applied to a first resistor divider sub-circuit including series resistors R1A and R2A. The center node of this first resistor divider sub-circuit is coupled to the first input of comparator 322 via diode D1. The voltage from converter circuit 304 is then converted to voltage. B The voltage is applied to a second resistor divider subcircuit, which includes series resistors R1B and R2B. The center node of this second resistor divider subcircuit is coupled to the first input of comparator 322 via diode D2. The second input of comparator 322 is coupled to reference voltage source 324. The resistor divider subcircuit scales the input voltage V. A V B To match the voltage input limit of comparator 322, diodes D1 and D2 separate the voltage of one input from the other. The scaled voltage applied to the first input of comparator 322 is V. A and V B The circuit selects a larger voltage to compare with the reference voltage source 324, and outputs the CTRL signal. Similar to... Figure 4B , Figure 5B The diodes D1 and D2 at the first input of comparator 322 can be replaced by a switch that is actively controlled, for example, by a selection signal from controller 108.

[0058] It should be clear that Figure 5A and Figure 5B Other variations of the sub-circuit selection circuit system shown can be used for Figure 3BThe UVLO circuit 124. Similarly, a sub-circuit selection circuit system can be used in the voltage regulator 122 to effectively determine which applied voltage V. A V B This will supply power to voltage regulator 122.

[0059] Figure 3A and Figure 3B A significant advantage of the circuit architecture shown is that the analog multiplexer and / or sub-circuit selection circuit system can be implemented within the auxiliary circuit 302, thereby eliminating the need for additional external circuitry for the voltage booster circuit or pre-charge circuit.

[0060] Selective voltage input to the gate driver circuit

[0061] Figure 3A and Figure 3B The implementation modifies the auxiliary circuit 302 to select the voltage V from the converter circuit 304 during startup. A V B The larger of the two is used as the power supply for auxiliary circuit 302. In the case where the normal boost power converter operates in reverse (i.e., in buck mode), the pre-charge circuit 204 can be eliminated in embodiments of the invention (see [link]). Figure 2A ).

[0062] A better understanding of the requirements for the pre-charge circuit 204 is useful, especially for power converters that include switched capacitor networks. Figure 6A This is a circuit diagram of a prior art converter circuit 600, which includes a single-phase symmetrical cascaded multiplier with a boost ratio of 1:5, and can be used as... Figure 1A An example of converter circuit 102. Converter circuit 600 is configured to operate at node V. X Receives an input voltage (e.g., 5 V) at node V, and at node V C5 The input voltage is converted to a higher output voltage (e.g., 25 V). The converter circuit 600 shown will be used in a known manner. Figure 1A The controller 108 controls it. Refer to converter circuit 600 and... Figure 1A Node V X Corresponding to input terminal T1 of converter circuit 102, node V C5 Corresponding to the output terminal T2 of converter circuit 102, and node V SS These correspond to the two terminals T1' and T2' of the converter circuit 102.

[0063] Cascaded multipliers are switched-capacitor networks that can provide high conversion gain. As used in this disclosure, the conversion gain (1) in the switched-capacitor network generates an output voltage (V) greater than the input voltage. OUT > VIN In the case of (1), it represents the voltage gain; or (2) in the case where the switched capacitor network generates an output voltage (V) less than the input voltage. IN > V OUT In the case of ), current gain is represented. Energy is transferred from the input to the output by cascading the multiplier through different topology states. Charge is transferred from the input voltage to the output voltage via charge transfer paths. The number and arrangement of capacitors in each topology state determine the conversion gain.

[0064] In the example shown, the converter circuit 600 includes five MOSFET switches M1 to M5 connected in series. Each MOSFET switch M1 to M5 may comprise a stack of MOSFETs connected in series, the MOSFETs having a common gate connection and being configured to function as a single switch. For ease of discussion of the switch order, switches M1, M3, and M5 will sometimes be collectively referred to as “odd switches”, and switches M2 and M4 will sometimes be collectively referred to as “even switches”.

[0065] The converter circuit 600 also includes a first "low-side" MOSFET phase switch M7 and a second "low-side" MOSFET phase switch M8, as well as a first "high-side" MOSFET phase switch M6 and a second "high-side" MOSFET phase switch M9. The low-side phase switches M7 and M8 can connect the first phase node P1 and the second phase node P2 to a potential V. SS (Usually circuit ground). High-side phase switches M6 and M9 can connect the first phase node P1 and the second phase node P2 to V. X For ease of discussion regarding the switching sequence, the high-side phase switch M6 and the low-side phase switch M8 are sometimes collectively referred to as "even-numbered phase switches," while the low-side phase switch M7 and the high-side phase switch M9 are sometimes collectively referred to as "odd-numbered phase switches."

[0066] The first pump capacitor C1 connects the first stacking node V between switch M1 and switch M2. C1 Connected to phase node P1. Similarly, the third pump capacitor C3 connects the third stack node V between switch M3 and switch M4. C3 Connected to phase node P1. The second pump capacitor C2 connects the second stack node V between switch M2 and switch M3. C2 Connected to phase node P2. Similarly, the fourth pump capacitor C4 connects the fourth stack node V between switch M4 and switch M5. C4 Connect to phase node P2. Fifth stack node V C5 Terminals connected to converter circuit 600

[0067] The converter circuit 600 shown has four stages. The first stage includes a switch M1 and a first stacking node V.C1 The first pump capacitor C1; the second stage includes switch M2 and second stack node V. C2 The second pump capacitor C2; the third stage includes switch M3 and third stack node V. C3 And the third pump capacitor C3; the fourth stage includes switch M4 and the fourth stack node V. C4 And the fourth pump capacitor C4. The fifth series switch M5 connects the fourth stage to the fifth stack node V. C5 .

[0068] The clock source in controller 108 generates non-overlapping clock waveforms φ1 and φ2, which are coupled to various switches M1 to M9 and control their on / off states. Controller 108 outputs a set of control signals 112 to converter circuit 600, causing the series switches M1 to M5, low-side phase switches M7 and M8, and high-side phase switches M6 and M9 to change states in a specific sequence. Therefore, converter circuit 600 repeatedly transitions between a first operating state and a second operating state at a selected frequency.

[0069] For example, during the first operating state defined by a clock waveform of φ1 with a logic "1" state and a clock waveform of φ2 with a logic "0" state, controller 108 (1) closes odd-numbered switches M1, M3, M5, low-side phase switch M7, and high-side phase switch M9; and (2) opens even-numbered switches M2, M4, high-side phase switch M6, and low-side phase switch M8. During the second operating state defined by a clock waveform of φ2 with a logic "1" state and a clock waveform of φ1 with a logic "0" state, controller 108 (1) opens odd-numbered switches M1, M3, M5, low-side phase switch M7, and high-side phase switch M9; and (2) closes even-numbered switches M2, M4, high-side phase switch M6, and low-side phase switch M8. Controller 108 controls and sequentially arranges the transitions of all switches M1 to M9 in such a manner that any necessary dead time required when transitioning between the first and second operating states is incorporated. As a result of alternating between the first and second operating states, the charge is multiplied in a known manner and from V X Pass to V C5 .

[0070] As is known in the art, switching signals are applied to MOSFET switches M1 to M9 via corresponding gate driver circuits G1 to G9 in order to provide an appropriate voltage level for timely turn-off (blocking) or turn-on (conduction) of each MOSFET switch. Figure 6B This is a block diagram of a prior art gate driver circuit 610. The gate driver circuit 610 includes a level shifter 612 coupled to an input source V. DDI Hehui VSSI Potential (sink V) SSI potentials), and coupled to the output source V DDO Hehui V SSO Potential. The level shifter 612 will input the switch signal V. SWI Transforming from one voltage domain to another. The level-shifted output voltage V of level shifter 612. LSO Coupled to gate driver 614, which is in V SWO V provided LSO A low-impedance version, and a timely manner to drive the associated MOSFET switch M. X The gate terminal.

[0071] Return to reference Figure 6A The converter circuit 600, with gate driver circuits G1 to G9 shown in simplified block form, is coupled to corresponding switches M1 to M9 and connected to the output source and sink potential. Each gate driver circuit G1 to G9 has a corresponding input switch signal EN1 to EN9 (one of clock waveforms φ1 or φ2), which controls the switching state of the corresponding switches M1 to M9. All gate driver circuits G1 to G9 are coupled to a common input source V. DDI Hehui V SSI Potential (not shown for clarity), wherein V generated from auxiliary circuit 110 DD Voltage coupled to common input source V DDI For power and area efficiency, the gate driver circuits G1 to G6 and G9 are coupled to node V of the converter circuit 600 itself. C1 To V C5 As the output source V DDO Hehui V SSO Potential. Figure 6A In a specific implementation, MOSFET switches M1 to M4, M6 to M9 are N-type transistors, while MOSFET switch M5 is a P-type transistor. This is also reflected in the output source V shown for each gate driver circuit G1 to G9. DDO Hehui V SSO At potential. Gate driver circuits G7 to G8 are coupled to V generated from auxiliary circuit 110. DD Voltage, used as the input source V for gate driver circuits G7 to G8 DDI Potential and output source V DDO Potential.

[0072] In the forward boost operation mode, due to the inherent body diode path connected in parallel with each of the switches M1 to M5, node V C1 To VC5 Initially (i.e., at startup), the pump pressure is increased to V. X The applied voltage is above, and eventually, sufficient output source V is reached. DDO Hehui V SSO The voltage is set for normal operation of the gate driver circuits G1 to G9, thereby allowing switches M1 to M5 to take over. However, in the reverse buck operation mode, the input voltage is applied to node V. C5 At this point, and the output voltage will be at node V. X Node V is generated at this location. X V C1 To V C4 It can be found in V SS At or near ground potential V SS It starts at ground potential; therefore, there is not yet a sufficient output source V. DDO Hehui V SSO The potential used for normal operation of the gate driver circuits G1 through G9 further exacerbates the cycle-start problem. Therefore, the pre-charge circuit 204 is typically used to apply an initial sufficient voltage from node V. C5 The input voltage at point V is provided to node V within the converter circuit 600. X V C1 To V C4 To provide sufficient output source V DDO Hehui V SSO The potential is used for the initial operation of gate drivers G1 to G9. After startup, the node V is then adequately supplied by the steady-state operation of the converter circuit 600. X V C1 To V C4 The voltage at the point, and therefore the pre-charge circuit 204 can be disabled or disconnected.

[0073] Figure 7A It is possible to be with Figure 6A The block diagram shows the converter circuit 600 combined with an improved gate driver circuit 700. The improved gate driver circuit 700 is similar in many respects to... Figure 6B The gate driver circuit 610. Therefore, the gate driver circuit 700 includes a level shifter 612, which is coupled to the input source V. DDI Hehui V SSI Potential, and coupled to the output source V DDO Hehui V SSO Potential. The level shifter 612 will input the switch signal V. SWI Transforming from one voltage domain to another. The level-shifted output voltage V of level shifter 612. LSO Coupled to gate driver 614, which is in VSWO The output provides low impedance and drives the associated MOSFET switch M in a timely manner. X The gate terminal.

[0074] Furthermore, the gate driver circuit 700 includes a selector 702 that functions as an analog multiplexer, allowing output sources V used within the gate driver circuit 700 to be selected. DDO Potential selection of two input voltages V DDO A or V DDO One of B. Selector 702 can be controlled, for example, by controller 108 (e.g., based on information about whether converter circuit 304 is operating in the forward or reverse direction), or by utilizing a similar Figure 4A The self-selected implementation method. Therefore, the gate driver circuit 700 is relative to the output source V. DDO A dual-voltage device with a potential. Once the input voltage V is coupled on by selector 702... DDO A or V DDO B, then the operation of the gate driver circuit 700 is basically the same as that of a conventional gate driver.

[0075] Figure 7B This is a circuit diagram of a modified converter circuit 720, which includes a single-phase symmetrical cascaded multiplier with a boost ratio of 1:5 and can be used as... Figure 1A An example of converter circuit 102. In the illustrated embodiment, gate driver circuits G1 to G3, G6, and G9 are Figure 7A An example of a gate driver circuit 700. In the illustrated embodiment, the first input (e.g., V) to each of the gate drivers G1 to G3, G6 and G9 is... DDO A) is with Figure 6A The same V in the example shown CX Node (i.e., V) C1 To V C4 The second input (e.g., V) to each of the gate drivers G1 to G3, G6, and G9 DDO B) is (in this level 4 example) applied to V C5 The reverse input voltage at the "reverse mode input node" (G4 and G5). Conventional single-source gate driver circuits can be... Figure 6B An example of the gate driver circuit 610, and remains coupled to V. C5 For their output source V DDO Potential, such as Figure 6A The example shown is the same. Conventional single-source gate driver circuits G7 and G8 can be... Figure 6B An example of the gate driver circuit 610, and also remains coupled to the V generated from the auxiliary circuit 110. DDVoltage for their input source V DDI Potential and output source V DDO Potential.

[0076] In the forward boost operation mode, selector 702 will select the corresponding stacked node V for the gate driver circuits G1 to G3, G6 and G9. C1 To V C4 As the output source V DDO Potential. However, during the reverse buck operation mode of the converter circuit 720's startup phase, selector 702 will select the reverse mode input node (V in this example) for the gate driver circuits G1 to G3, G6, and G9. C5 ) as output source V DDO Potential, until at stack node V C1 To V C4 Sufficient voltage levels have been developed to support the gate driver circuitry. Therefore, there is a sufficient output source V regardless of whether it is in forward or reverse operation mode. DDO A potential can be applied to each of the gate driver circuits G1 through G9. The improved gate driver circuit 700 thus effectively enables the illustrated converter circuit 720 to be self-biased at startup.

[0077] Figure 7A and Figure 7B A significant advantage of the improved gate driver circuit 700 and circuit architecture shown is that the circuit system can be implemented without the need for additional external circuitry such as the precharge circuit 204.

[0078] While single-phase symmetrical cascaded multipliers have been used in converter circuits 600 and 720 to illustrate the problem solved by the improved gate driver circuit 700, it should be noted that the use of the improved gate driver circuit 700 is not limited to switched capacitor networks or charge pumps. This aspect of the invention can also be applied to inductor-based regulators using transistor switches having one or more series-stacked switching stages.

[0079] Combined implementation methods

[0080] Figure 3A The implementation shown in the example eliminates the need for an external voltage booster circuit 202. Figure 7A and 7B The illustrated embodiment eliminates the need for an external pre-charge circuit 204. It should be understood that embodiments of the invention can include both the inventive concept of the external voltage booster circuit 202 and the external pre-charge circuit 204, thereby eliminating the need for both. Therefore, the combined embodiment allows the power converter to be started and operated in a reverse unidirectional or bidirectional manner with zero external components.

[0081] method

[0082] Another aspect of the invention includes a method for powering an auxiliary circuit, selecting a sub-circuit of the auxiliary circuit, and powering a dual-voltage input gate driver.

[0083] For example, Figure 8 This is a flowchart 800 illustrating a method for supplying power to an auxiliary circuit of a power converter. The method includes: providing a power converter including converter circuitry having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage (block 802); coupling an auxiliary circuitry to the first and second terminals of the converter circuitry (block 804); and selectively coupling the auxiliary circuitry to the greater of the first or second voltage to supply power to the auxiliary circuitry (block 806). In an alternative method, the selection of the first or second voltage may be based on knowledge of existing forward or reverse configurations of the converter circuitry.

[0084] As another example, Figure 9 This is a method flowchart 900 illustrating a method of selecting a sub-circuit from a plurality of sub-circuits in an auxiliary circuit of a power converter. The power converter includes providing a power converter comprising converter circuitry having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage (block 902); coupling at least a first sub-circuit of the auxiliary circuitry to the first terminal of the converter circuitry (block 904); coupling at least a second sub-circuit of the auxiliary circuitry to the second terminal of the converter circuitry (block 906); and selectively coupling at least one first sub-circuit or at least one second sub-circuit to the greater of the first voltage or the second voltage to generate an output for the auxiliary circuitry (block 908).

[0085] As yet another example, Figure 10 This is a method flowchart 1000 illustrating a method of providing power to the gate driver circuit of a corresponding transistor switch of a power converter. The method includes selectively coupling a level shifter and a gate driver to one of a first output source potential or a second output source potential, wherein the first output source potential originates from a first voltage node of the power converter circuit, and the second output source potential originates from a different second voltage node of the power converter circuit (block 1002).

[0086] These methods can be used together. For example, Figure 8 This method can be used in the first part of the auxiliary circuit. Figure 9 This method can be used in the second part of the auxiliary circuit. As another example, Figure 10 The method can be with Figure 8 Methods and / or Figure 9 The methods are used in combination.

[0087] Manufacturing technology and options

[0088] As used in this disclosure, the term "MOSFET" includes any field-effect transistor (FET) having an insulated gate (whose voltage determines the transistor's conductivity), and includes an insulated gate having a metallic or metalloid, insulator, and / or semiconductor structure. The terms "metal" or "metalloid" include at least one conductive material (e.g., aluminum, copper, or other metals, or highly doped polycrystalline silicon, graphene, or other conductors), "insulator" includes at least one insulating material (e.g., silicon oxide or other dielectric material), and "semiconductor" includes at least one semiconductor material.

[0089] As used in this disclosure, the term "radio frequency" (RF) refers to an oscillation rate in the range of about 3 kHz to about 300 GHz. The term also includes frequencies used in wireless communication systems. RF frequencies can be the frequencies of electromagnetic waves or the frequencies of alternating voltage or current in a circuit.

[0090] Various embodiments of the present invention can be implemented to meet various specifications. Unless otherwise stated above, the selection of suitable component values ​​is a matter of design choice. Various embodiments of the present invention can be implemented using any suitable integrated circuit (IC) technology (including, but not limited to, MOSFET structures) or in hybrid or discrete circuit form. Integrated circuit embodiments can be fabricated using any suitable substrate and process (including, but not limited to, standard bulk silicon, silicon-on-insulator (SOI), and silicon-on-sapphire (SOS)). Unless otherwise stated above, embodiments of the present invention can be implemented using other transistor technologies, such as bipolar, LDMOS, BCD, GaAs HBT, GaN HEMT, GaAs pHEMT, and MESFET technologies. However, embodiments of the present invention are particularly useful when fabricated using SOI or SOS-based processes or when fabricated using processes with similar characteristics. Fabrication in CMOS using SOI or SOS processes enables circuits to have low power consumption, the ability to withstand high power signals during operation due to FET stacking, good linearity, and high-frequency operation (i.e., radio frequencies up to and exceeding 50 GHz). Monolithic IC implementations are particularly useful because parasitic capacitance can typically be kept low (or kept to a minimum, consistent across all cells, allowing for compensation of parasitic capacitance) through careful design.

[0091] Depending on specific specifications and / or implementation technologies (e.g., NMOS, PMOS, or CMOS, and enhancement-mode or depletion-mode transistor devices), voltage levels and / or the polarity of voltage and / or logic signals can be reversed. The voltage, current, and power handling capabilities of components can be adjusted as needed, for example, by adjusting device size, "stacking" components (especially FETs) in series to handle higher voltages, and / or using multiple components in parallel to handle higher currents. Additional circuit components can be added to enhance the capabilities of the disclosed circuit and / or to provide additional functionality without significantly altering the function of the disclosed circuit.

[0092] The circuits and devices according to the invention can be used alone or in combination with other components, circuits, and devices. Embodiments of the invention can be manufactured as integrated circuits (ICs), which can be packaged in IC packages and / or modules for ease of handling, manufacturing, and / or improved performance. In particular, IC embodiments of the invention are frequently used in modules in which one or more such ICs are combined with other circuit blocks (e.g., filters, passive components, and possible additional ICs) into a single package. The ICs and / or modules are then typically combined with other components, usually on a printed circuit board, to form end products such as cell phones, laptops, or tablets, or to form higher-level modules that can be used in various products (e.g., vehicles, test equipment, medical devices, etc.). Through various configurations of modules and components, such ICs typically enable a communication mode, often wireless communication.

[0093] in conclusion

[0094] Many embodiments of the present invention have been described. It should be understood that various modifications can be made without departing from the spirit and scope of the invention. For example, some of the steps described above may be order-independent and therefore may be performed in a different order than that described. Furthermore, some of the steps described above may be optional. The various actions described with respect to the above method may be performed in a repetitive, serial, or parallel manner.

[0095] It should be understood that the foregoing description is intended to illustrate, rather than limit, the scope of the invention, which is defined by the scope of the appended claims, and other embodiments are within the scope of the claims. In particular, the scope of the invention includes any and all possible combinations of one or more of the methods, machines, manufactures, or compositions of matter set forth in the appended claims. (Note that the bracketed designations of claim elements are intended to readily refer to such elements and do not in themselves indicate a particular order of requirements or an enumeration of elements; furthermore, such designations may be repeated in dependent claims as references to additional elements without being considered as the initiation of a conflicting sequence of designations.)

Claims

1. An auxiliary circuit configured to provide various voltages to a converter circuit, the auxiliary circuit including a first terminal configured to be selectively coupled to a first voltage, a second terminal configured to be selectively coupled to a second voltage, and at least one input voltage selector having a first input coupled to the first terminal and a second input coupled to the second terminal, the at least one input voltage selector further including an output; in, The at least one input voltage selector includes: (1) a first diode and a first resistor connected in series between the first terminal and the output; and (2) a second diode and a second resistor connected in series between the second terminal and the output; and The at least one input voltage selector is configured to: (1) selectively couple to the larger of the first voltage or the second voltage during the startup phase of the auxiliary circuit to provide power from the output to the auxiliary circuit, and (2) selectively couple to the smaller of the first voltage or the second voltage during the steady-state operation phase of the auxiliary circuit to provide power from the output to the auxiliary circuit, wherein the selected smaller voltage reaches or exceeds a specified minimum voltage for the steady-state operation phase.

2. The auxiliary circuit according to claim 1, wherein, The auxiliary circuitry includes one or more sub-circuits coupled to the at least one input voltage selector.

3. The auxiliary circuit according to claim 1, wherein, The at least one input voltage selector is an analog multiplexer.

4. The auxiliary circuit according to claim 1, wherein, The at least one input voltage selector is configured to automatically select either the first voltage or the second voltage to provide power to the auxiliary circuit.

5. The auxiliary circuit according to claim 1, wherein, The at least one input voltage selector is coupled to a control signal that selects either the first voltage or the second voltage to provide power to the auxiliary circuit.

6. A power converter, comprising: A converter circuit having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage; An auxiliary circuit, configured to provide various voltages to other circuit systems; as well as At least one input voltage selector having a first input coupled to a first terminal of the converter circuit, a second input coupled to a second terminal of the converter circuit, and an output, the at least one input voltage selector comprising: (1) a first diode and a first resistor connected in series between the first terminal and the output, and (2) a second diode and a second resistor connected in series between the second terminal and the output; The at least one input voltage selector is configured to: (1) selectively couple to the larger of the first voltage or the second voltage during the startup phase of the auxiliary circuit to provide power from the output to the auxiliary circuit, and (2) selectively couple to the smaller of the first voltage or the second voltage during the steady-state operation phase of the auxiliary circuit to provide power from the output to the auxiliary circuit, wherein the selected smaller voltage reaches or exceeds a specified minimum voltage for the steady-state operation phase.

7. The power converter according to claim 6, wherein, The auxiliary circuitry includes one or more sub-circuits coupled to the at least one input voltage selector.

8. The power converter according to claim 6, wherein, The at least one input voltage selector is an analog multiplexer.

9. The power converter according to claim 6, wherein, The at least one input voltage selector is configured to automatically select either the first voltage or the second voltage to provide power to the auxiliary circuit.

10. The power converter according to claim 6, wherein, The at least one input voltage selector is coupled to a control signal that selects either the first voltage or the second voltage to provide power to the auxiliary circuit.

11. The power converter according to claim 6, further comprising: A gate driver circuit, comprising a level shifter and a gate driver, the level shifter and the gate driver being configured to be selectively coupled to one of a first output source potential or a second output source potential, and configured to convert an input switching signal having a first voltage into an output switching signal having a second voltage, wherein the gate driver circuit is configured to control the switching of a corresponding transistor of the converter circuit, and the first output source potential originates from a first voltage node of the converter circuit, the second output source potential originating from a second voltage node of the converter circuit, the second voltage node being different from the first voltage node.

12. An auxiliary circuit configured to provide various voltages to a converter circuit, the auxiliary circuit comprising: The first terminal is configured to be selectively coupled to a first voltage; The second terminal is configured to be selectively coupled to a second voltage; A first sub-circuit, the first sub-circuit having an input coupled to the first terminal and a first output; The second sub-circuit has an input coupled to the second terminal and a second output; as well as An input voltage selector having a first input coupled to a first output of a first sub-circuit, a second input coupled to a second output of a second sub-circuit, and a third output, wherein the input voltage selector is configured to: (1) during the startup phase of the auxiliary circuit, select the first sub-circuit or the second sub-circuit coupled to the larger of the first voltage or the second voltage, and provide power from the selected first sub-circuit or the second sub-circuit to the auxiliary circuit from the third output; and (2) during the steady-state operation phase of the auxiliary circuit, select the first sub-circuit or the second sub-circuit coupled to the smaller of the first voltage or the second voltage, and provide power from the selected first sub-circuit or the second sub-circuit to the auxiliary circuit from the third output, wherein the selected smaller voltage reaches or exceeds a specified minimum voltage for the steady-state operation phase.

13. The auxiliary circuit according to claim 12, wherein, The first sub-circuit or the second sub-circuit coupled to the greater of the first voltage or the second voltage is selectively configured to generate an output for the auxiliary circuit.

14. The auxiliary circuit according to claim 12, wherein, The auxiliary circuit is coupled to a control signal that selects either the first sub-circuit or the second sub-circuit to generate an output for the auxiliary circuit.

15. A power converter, comprising: Converter circuit; An auxiliary circuit, configured to provide various voltages to the converter circuit, includes: The first terminal is configured to be selectively coupled to a first voltage; The second terminal is configured to be selectively coupled to a second voltage; A first sub-circuit, the first sub-circuit having an input coupled to the first terminal and a first output; The second sub-circuit has an input coupled to the second terminal and a second output; An input voltage selector having a first input coupled to a first output of a first sub-circuit, a second input coupled to a second output of a second sub-circuit, and a third output, wherein the input voltage selector is configured to: (1) during the startup phase of the auxiliary circuit, select the first sub-circuit or the second sub-circuit coupled to the larger of the first voltage or the second voltage, and provide power from the selected first sub-circuit or the second sub-circuit to the auxiliary circuit from the third output; and (2) during the steady-state operation phase of the auxiliary circuit, select the first sub-circuit or the second sub-circuit coupled to the smaller of the first voltage or the second voltage, and provide power from the selected first sub-circuit or the second sub-circuit to the auxiliary circuit from the third output, wherein the selected smaller voltage reaches or exceeds a specified minimum voltage for the steady-state operation phase.

16. The power converter according to claim 15, wherein, The first sub-circuit or the second sub-circuit coupled to the greater of the first voltage or the second voltage is selectively configured to provide an output for the auxiliary circuit.

17. The power converter according to claim 15, wherein, The auxiliary circuit is coupled to a control signal that selects either the first sub-circuit or the second sub-circuit to generate an output for the auxiliary circuit.

18. The power converter of claim 15, further comprising: A gate driver circuit, comprising a level shifter and a gate driver, the level shifter and the gate driver being configured to be selectively coupled to one of a first output source potential or a second output source potential, and configured to convert an input switching signal having a first voltage into an output switching signal having a second voltage, wherein the gate driver circuit is configured to control the switching of a corresponding transistor of the converter circuit, and the first output source potential originates from a first voltage node of the converter circuit, the second output source potential originating from a second voltage node of the converter circuit, the second voltage node being different from the first voltage node.

19. A method for supplying power to an auxiliary circuit of a power converter, the power converter including a converter circuit having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage, the method comprising: The auxiliary circuit is coupled to the first and second terminals of the converter circuit; During the startup phase of the auxiliary circuit, the larger of the first voltage or the second voltage is selectively coupled to provide power to the auxiliary circuit; as well as During the steady-state operation phase of the auxiliary circuit, the smaller of the first voltage or the second voltage is selectively coupled to provide power to the auxiliary circuit, while the selected smaller voltage reaches or exceeds a specified minimum voltage for the steady-state operation phase.

20. An auxiliary circuit configured to provide various voltages and / or signals to a converter circuit control circuit system and a converter circuit having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage, the auxiliary circuit including at least one input voltage selector configured to be coupled to the first terminal and the second terminal of the converter circuit, and coupled to the auxiliary circuit, and the at least one input voltage selector configured to (1) selectively couple to the larger of the first voltage or the second voltage during a startup phase of the auxiliary circuit to provide power to the auxiliary circuit, and (2) selectively couple to the smaller of the first voltage or the second voltage during a steady-state operation phase of the auxiliary circuit to provide power to the auxiliary circuit, wherein the selected smaller voltage reaches or exceeds a specified minimum voltage of the steady-state operation phase.

21. The auxiliary circuit according to claim 20, wherein, The auxiliary circuitry includes one or more sub-circuits coupled to a corresponding input voltage selector.

22. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector is an analog multiplexer.

23. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector is configured to automatically select either the first voltage or the second voltage to provide power to the auxiliary circuit.

24. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector is coupled to a control signal that selects either the first voltage or the second voltage to provide power to the auxiliary circuit.

25. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first diode, which is connected in series with a first resistor, and the series-coupled first diode and first resistor are connected in series between the first input terminal and the output terminal; and A second diode is connected in series with a second resistor, and the series-coupled second diode and the second resistor are connected in series between the second input terminal and the output terminal.

26. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first switch, which is connected in series between the first input terminal and the output terminal; and The second switch is connected in series between the second input terminal and the output terminal.

27. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first diode, coupled in parallel with a first switch, and the parallel-coupled first diode and the first switch, coupled in series between the first input terminal and the output terminal; and The second diode is coupled in parallel with the second switch, and the parallel-coupled second diode and the second switch are coupled in series between the second input terminal and the output terminal.

28. The auxiliary circuit according to claim 20, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first resistor divider is coupled to the first input terminal and has a first center node; A second resistor divider is coupled to the first input terminal and has a second center node; A comparator having a first input, a second input, and an output coupled to the output terminal; A first diode is coupled between the first center node and the first input of the comparator; A second diode, coupled between the second center node and the first input of the comparator; and A reference voltage source is coupled to the second input of the comparator.

29. The auxiliary circuit of claim 20, further comprising at least one gate driver circuit, each gate driver circuit coupled to a corresponding transistor switch of the converter circuit, each gate driver circuit including a level shifter and a gate driver, the level shifter and the gate driver being configured to selectively couple to one of a first output source potential or a second output source potential, and being configured to convert an input switching signal having a first level voltage into an output switching signal having a second level voltage, wherein... Each gate driver circuit is configured to control the corresponding transistor switch of the converter circuit, and the first output source potential comes from a first voltage node of the converter circuit, and the second output source potential comes from a second voltage node of the converter circuit, which is different from the first voltage node.

30. A power converter, comprising: A converter circuit having a first terminal configured to be selectively coupled to a first voltage and a second terminal configured to be selectively coupled to a second voltage; An auxiliary circuit, configured to provide various voltages and / or signals to other circuit systems; At least one input voltage selector coupled to the first and second terminals of the converter circuit and coupled to the auxiliary circuit, and the at least one input voltage selector being configured to (1) selectively couple to the larger of the first voltage or the second voltage during the startup phase of the auxiliary circuit to provide power to the auxiliary circuit, and (2) selectively couple to the smaller of the first voltage or the second voltage during the steady-state operation phase of the auxiliary circuit to provide power to the auxiliary circuit, wherein the selected smaller voltage reaches or exceeds a specified minimum voltage for the steady-state operation phase.

31. The power converter according to claim 30, wherein, The auxiliary circuitry includes one or more sub-circuits coupled to a corresponding input voltage selector.

32. The power converter according to claim 30, wherein, At least one input voltage selector is an analog multiplexer.

33. The power converter according to claim 30, wherein, At least one input voltage selector is configured to automatically select either the first voltage or the second voltage to provide power to the auxiliary circuit.

34. The power converter according to claim 30, wherein, At least one input voltage selector is coupled to a control signal that selects either the first voltage or the second voltage to provide power to the auxiliary circuit.

35. The power converter of claim 30, further comprising at least one gate driver circuit, each gate driver circuit coupled to a corresponding transistor switch of the converter circuit, each gate driver circuit including a level shifter and a gate driver, the level shifter and the gate driver being configured to selectively couple to one of a first output source potential or a second output source potential, and being configured to convert an input switching signal having a first level voltage into an output switching signal having a second level voltage, wherein... Each gate driver circuit is configured to control the corresponding transistor switch of the converter circuit, and the first output source potential comes from a first voltage node of the converter circuit, and the second output source potential comes from a second voltage node of the converter circuit, which is different from the first voltage node.

36. The power converter according to claim 30, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first diode, which is connected in series with a first resistor, and the series-coupled first diode and first resistor are connected in series between the first input terminal and the output terminal; and A second diode is connected in series with a second resistor, and the series-coupled second diode and the second resistor are connected in series between the second input terminal and the output terminal.

37. The power converter according to claim 30, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first switch, which is connected in series between the first input terminal and the output terminal; and The second switch is connected in series between the second input terminal and the output terminal.

38. The power converter according to claim 30, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first diode, coupled in parallel with a first switch, and the parallel-coupled first diode and the first switch, coupled in series between the first input terminal and the output terminal; and The second diode is coupled in parallel with the second switch, and the parallel-coupled second diode and the second switch are coupled in series between the second input terminal and the output terminal.

39. The power converter according to claim 30, wherein, At least one input voltage selector includes: First input terminal, second input terminal, and output terminal; A first resistor divider is coupled to the first input terminal and has a first center node; A second resistor divider is coupled to the first input terminal and has a second center node; A comparator having a first input, a second input, and an output coupled to the output terminal; A first diode is coupled between the first center node and the first input of the comparator; A second diode, coupled between the second center node and the first input of the comparator; and A reference voltage source is coupled to the second input of the comparator.

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