Direct-current port control method and device of high-frequency alternating-current bus type electric energy router

Abstract

The application discloses a DC port control method and device of a high-frequency AC bus type electric energy router. By collecting high-frequency bus information and high-frequency inductor current information in the port, the reactive power transmitted in the modular multi-active bridge of the core level of the electric energy router is inhibited, so that the effective value of the inductor current is reduced, and the system efficiency is improved. The problems of great current stress generated in the modular multi-active bridge when the voltage conversion ratios of the ports are different under single phase-shifting control, a large amount of reactive power transmission between the ports, and system efficiency reduction are solved.

Description

Technical Field

[0001] This application relates to the field of power system distribution network technology, and in particular to a DC port control method and device for a high-frequency AC bus-type power router. Background Technology

[0002] The integration of distributed renewable energy and energy storage devices into the grid places higher demands on the distribution network. Unlike the top-down generation structure of traditional power systems, the energy flow in the new distribution network is complex, requiring more flexible and stable distribution equipment to coordinate and optimize the integrated "source-grid-load-storage" power system. Power routers employing new power electronics technologies, with their stable dispatching functions and flexible control capabilities, have become the hub of the new distribution network. In addition to energy dispatching, power routers can also achieve port electrical isolation and energy conversion through multi-stage conversion structures. Current power routers also exhibit intelligent conversion characteristics such as multi-port, multi-cascade, multi-flow direction, and multi-form, while also possessing functions such as reactive power compensation, harmonic mitigation, and plug-and-play functionality.

[0003] The related technology is based on the analysis of the topology and control of a four-port power router on a high-frequency AC bus. The core of the high-frequency bus power router is a modular multi-active bridge, and each port adopts single-phase shift control. Under single-phase shift control, when the voltage conversion ratios of each port are different, a large current stress will be generated inside the modular multi-active bridge, and a large amount of reactive power will be transferred between the ports, resulting in a decrease in system efficiency. Summary of the Invention

[0004] This application provides a DC port control method and device for a high-frequency AC bus-type power router to solve the problems of large current stress generated inside the modular multi-active bridge and a large amount of reactive power transmission between ports, resulting in a decrease in system efficiency when the voltage conversion ratios of each port are different under single-phase-shift control.

[0005] The first aspect of this application provides a DC port control method for a high-frequency AC bus-type power router. The high-frequency AC bus-type power router includes multiple power sub-modules connected via a high-frequency bus. These power sub-modules are cascaded or connected in parallel to form multiple DC ports with multiple voltage and power levels. The DC port control method includes the following steps: modulating the multiple DC ports using a 50% duty cycle phase-shift modulation method, with the switching signals of the power semiconductor devices in the upper and lower bridge arms of the full-bridge DC port being mutually inverted; sampling the high-frequency bus voltage and high-frequency bus current, and treating the high-frequency bus as a square wave source. The topology of the multiple DC ports is simplified, and a loop voltage equation relating the high-frequency bus voltage, high-frequency inductor current, and high-frequency inductance is established for the simplified DC ports. After transforming the loop voltage equation to remove the high-frequency component, a phase-locked loop is added, and the q-axis component of the high-frequency bus voltage is set to 0 to obtain the d-axis component of the high-frequency bus voltage. A Park transformation is performed on the high-frequency inductor current to obtain the dq-axis current component of the high-frequency inductor current. PI control is added to the d-axis component of the high-frequency bus voltage and the dq-axis current component of the high-frequency inductor current to obtain the dq-axis voltage component of the DC port.

[0006] Optionally, in one embodiment of this application, the high-frequency bus voltage is the sum of the AC output voltages of each DC port.

[0007] Optionally, in one embodiment of this application, the high-frequency bus voltage is:

[0008]

[0009] Among them, v sk The three-level AC voltage output from port k to the high-frequency bus side, l k V is the inductance coefficient of port k, N is the number of DC ports, and V is the inductance coefficient of port k. k ω is the stable DC voltage value at port k. s Let α be the switching angular frequency. k β is the inner phase shift angle of the DC port k. k The outward phase shift angle of the DC port k.

[0010] Optionally, in one embodiment of this application, the loop voltage equation relating the high-frequency bus voltage, the high-frequency bus current, and the high-frequency inductor established for the simplified DC port is as follows:

[0011]

[0012] Among them, V dc For the port DC voltage, α s ω is the inner phase shift angle of the DC port. sβ is the switching angular frequency. s V is the outward phase shift angle of the DC port. H β represents the fundamental amplitude of the high-frequency bus voltage. H The fundamental phase of the high-frequency bus voltage, p is the differential operator, L is the inductance, and I is the voltage. L β is the fundamental amplitude of the inductor current. L This is the phase of the fundamental frequency of the inductor current.

[0013] Optionally, in one embodiment of this application, the dq-axis voltage component of the DC port is:

[0014]

[0015] Among them, i Ld i is the d-axis component of the inductor current. Lq v is the q-axis component of the inductor current. Hd v represents the d-axis component of the fundamental amplitude of the high-frequency bus voltage. Hq K represents the q-axis component of the fundamental amplitude of the high-frequency bus voltage. p K is the proportional coefficient of the current PI controller. i is the integral coefficient of the current PI controller.

[0016] A second aspect of this application provides a DC port control device for a high-frequency AC bus-type power router. The high-frequency AC bus-type power router includes multiple power sub-modules connected via a high-frequency bus. These power sub-modules are cascaded or connected in parallel to form multiple DC ports with multiple voltage and power levels. The DC port control device includes: a modulation module for modulating the multiple DC ports using a 50% duty cycle phase-shift modulation method, wherein the switching signals of the power semiconductor devices in the upper and lower bridge arms of the full-bridge of the DC ports are mutually inverted; and a sampling module for sampling the high-frequency bus voltage and high-frequency bus current, treating the high-frequency bus as a square wave source. The topology of the multiple DC ports is simplified, and a loop voltage equation relating the high-frequency bus voltage, high-frequency inductor current, and high-frequency inductance is established for the simplified DC ports. A control module is used to transform the loop voltage equation to remove high-frequency components, add a phase-locked loop, set the q-axis component of the high-frequency bus voltage to 0 to obtain the d-axis component of the high-frequency bus voltage, perform a Park transformation on the high-frequency inductor current to obtain the dq-axis current component of the high-frequency inductor current, and add PI control to the d-axis component of the high-frequency bus voltage and the dq-axis current component of the high-frequency inductor current to obtain the dq-axis voltage component of the DC port.

[0017] Optionally, in one embodiment of this application, the high-frequency bus voltage is the sum of the AC output voltages of each DC port.

[0018] Optionally, in one embodiment of this application, the high-frequency bus voltage is:

[0019]

[0020] Among them, v sk The three-level AC voltage output from port k to the high-frequency bus side, l k V is the inductance coefficient of port k, N is the number of DC ports, and V is the inductance coefficient of port k. k ω is the stable DC voltage value at port k. s Let α be the switching angular frequency. k β is the inner phase shift angle of the DC port k. k The outward phase shift angle of the DC port k.

[0021] A third aspect of this application provides an electronic device, including: a memory, a processor, and a computer program stored in the memory and executable on the processor, wherein the processor executes the program to perform DC port control of a high-frequency AC bus-type power router as described in the above embodiments.

[0022] A fourth aspect of this application provides a computer-readable storage medium having a computer program stored thereon, which is executed by a processor to perform DC port control of a high-frequency AC bus-type power router as described in the above embodiments.

[0023] The DC port control method and apparatus of this application for a high-frequency AC bus-type power router utilizes high-frequency bus information and high-frequency inductor current information to calculate the DC port voltage and control the DC port, effectively reducing the reactive power of each port. This avoids the problem of large current stress generated inside the modular multi-active bridge and significant reactive power transmission between ports, which leads to a decrease in system efficiency when the voltage conversion ratios of different ports differ under single-phase-shift control.

[0024] Additional aspects and advantages of this application will be set forth in part in the description which follows, and in part will be obvious from the description, or may be learned by practice of this application. Attached Figure Description

[0025] The above and / or additional aspects and advantages of this application will become apparent and readily understood from the following description of the embodiments taken in conjunction with the accompanying drawings, wherein:

[0026] Figure 1 This is a flowchart of a DC port control method for a high-frequency AC bus-type power router according to an embodiment of this application;

[0027] Figure 2 This is a topology diagram of a multi-port high-frequency AC bus type power router provided according to an embodiment of this application;

[0028] Figure 3 This is a power submodule structure diagram of a multi-port high-frequency AC bus type power router provided according to an embodiment of this application;

[0029] Figure 4 This is an equivalent structural diagram of a multi-port high-frequency AC bus type power router provided according to an embodiment of this application under a corresponding modulation scheme;

[0030] Figure 5 This is an equivalent structural diagram of a single DC port of a multi-port high-frequency AC bus type power router provided according to an embodiment of this application;

[0031] Figure 6 This is a flowchart illustrating the frequency selection and filtering process for a high-frequency periodic physical quantity according to an embodiment of this application.

[0032] Figure 7 A method for providing an embodiment of this application Figure 5 A block diagram of the novel control strategy proposed by the equivalent structure diagram;

[0033] Figure 8 The DC voltage V at each port in the simulation according to the embodiments of this application dc and DC current I dc Waveform diagram;

[0034] Figure 9 The full-bridge output voltage v at each port in the simulation according to the embodiments of this application. s and inductor current i L Overall waveform diagram;

[0035] Figure 10 The full-bridge output voltage V at each port after port 2 is switched to reactive power control in the simulation according to the embodiments of this application. s and inductor current i L Detailed waveform diagram;

[0036] Figure 11 The full-bridge output voltage V at each port after port 3 is switched to reactive power control in the simulation according to the embodiments of this application. s and inductor current i L Detailed waveform diagram;

[0037] Figure 12 The full-bridge output voltage V at each port after port 4 is switched to reactive power control in the simulation according to the embodiments of this application. s and inductor current i L Detailed waveform diagram;

[0038] Figure 13 To simulate the active current i at each port according to the embodiments of this applicationd With reactive current i q Waveform diagram;

[0039] Figure 14 This is a waveform diagram of the fundamental reactive power at each port in a simulation provided according to an embodiment of this application;

[0040] Figure 15 This is an example diagram of a DC port control device for a high-frequency AC bus type power router according to an embodiment of this application;

[0041] Figure 16 A schematic diagram of the structure of the electronic device provided in the application embodiment. Detailed Implementation

[0042] The embodiments of this application are described in detail below. Examples of these embodiments are shown in the accompanying drawings, wherein the same or similar reference numerals denote the same or similar elements or elements having the same or similar functions throughout. The embodiments described below with reference to the accompanying drawings are exemplary and intended to explain this application, and should not be construed as limiting this application.

[0043] Figure 1 This is a flowchart of a DC port control method for a high-frequency AC bus-type power router according to an embodiment of this application.

[0044] like Figure 1 As shown, the DC port control method of this high-frequency AC bus type power router includes the following steps:

[0045] In step S101, multiple DC ports are modulated using a phase-shift modulation method with a 50% duty cycle, and the switching signals of the power semiconductor devices in the upper and lower bridge arms of the full bridge of the DC ports are reversed.

[0046] like Figure 2 As shown, the topology of a high-frequency bus-type power router core-level modular multi-active bridge is illustrated. The high-frequency AC bus-type power router includes multiple power sub-modules (SMs) connected via a high-frequency bus. These power sub-modules are cascaded or connected in parallel to form multiple DC ports with multiple voltage and power levels. For example... Figure 3 As shown, the power submodule contains DC capacitors, full-bridge power semiconductor devices, and a high-frequency transformer with leakage inductance. Theoretically, the number of DC ports is unlimited, and electrical isolation is achieved through the high-frequency transformer within the power submodule. Some DC ports can be connected to the AC grid or AC loads via front-end rectification or back-end inversion, thus forming a power router with multiple voltage levels and voltage configurations.

[0047] To address the issue that related technologies employ single-phase-shift control for each port, which leads to significant current stress and reactive power transfer between ports when the voltage conversion ratios differ, resulting in reduced system efficiency, this application, based on frequency domain theory, adopts a 50% duty cycle phase-shift modulation method for each DC port. The switching signals of the power semiconductor devices in the upper and lower arms of the full bridge are mutually inverted, and the phase difference between the switching signals of S1 and S4 is the inner phase-shift angle α of that DC port. Let the midpoint of the inner phase-shift angle of port 1 be the phase zero, and the phase lag between the midpoint of the inner phase-shift angle of the other ports and the phase zero be the outer phase-shift angle β of that DC port.

[0048] In step S102, the high-frequency bus voltage and high-frequency bus current are sampled, the high-frequency bus is regarded as a square wave source, the topology of multiple DC ports is simplified, and the loop voltage equation of the relationship between the high-frequency bus voltage, high-frequency inductor current and high-frequency inductor is established for the simplified DC ports.

[0049] Assuming the DC voltage at the port is a stable value V, and taking the midpoint of the phase shift angle within the port as the origin of the time axis, the voltage output from the port to the high-frequency bus is a three-level quasi-square wave. In this case, the topology of the modular multi-active bridge can be represented as follows: Figure 4 As shown.

[0050] Let ω s Given the switching angular frequency, the three-level AC voltage output from port i to the high-frequency bus can be expressed as:

[0051]

[0052] The inductance coefficient of port i is redefined as follows:

[0053]

[0054] The high-frequency bus voltage is formed by the superposition of the AC output voltages at each port, and its form is a multi-level AC square wave, which can be represented as:

[0055]

[0056] If we consider the high-frequency bus as a square wave source, then for any port, its topology can be simplified to: Figure 5 As shown.

[0057] Establish the loop voltage equation:

[0058] v s =v H -Li L (4)

[0059] According to equation (3), let the high-frequency bus voltage be:

[0060] vH (t)=V H sin(ω s t-β H )+O[sinω s t](5)

[0061] Where V H β represents the fundamental amplitude of the high-frequency bus voltage. H This is its fundamental phase. Similarly, the high-frequency bus current can be expressed as:

[0062] i L (t)=I L sin(ω s t-β L )+O[sinω s t](6)

[0063] Among them I L β is the fundamental amplitude of the inductor current. L Let its fundamental phase be denoted as . Considering only the fundamental components of each physical quantity, equation (4) can be expressed as:

[0064]

[0065] Among them, V dc For the port DC voltage, α s ω is the inner phase shift angle of the DC port. s β is the switching angular frequency. s V is the outward phase shift angle of the DC port. H β represents the fundamental amplitude of the high-frequency bus voltage. H The fundamental phase of the high-frequency bus voltage, p is the differential operator, L is the inductance, and I is the voltage. L β is the fundamental amplitude of the inductor current. L This is the phase of the fundamental frequency of the inductor current.

[0066] In step S103, the loop voltage equation is transformed to remove the high-frequency component, and a phase-locked loop is added to set the q-axis component of the high-frequency bus voltage to 0, thereby obtaining the d-axis component of the high-frequency bus voltage. The high-frequency inductor current is transformed by Park to obtain the dq-axis current component of the high-frequency inductor current. PI control is added to the d-axis component of the high-frequency bus voltage and the dq-axis current component of the high-frequency inductor current to obtain the dq-axis voltage component of the DC port.

[0067] like Figure 6 As shown, based on the above embodiment, multiply both sides of (7) by 2sinω s t, has:

[0068]

[0069] After filtering out high-frequency components, equation (8) becomes:

[0070]

[0071] Similarly, multiply both sides of (7) by -2cosω s After filtering out the high-frequency components, we have:

[0072]

[0073] The following definitions apply to (9) and (10):

[0074]

[0075] In summary, we have:

[0076]

[0077] Adding a phase-locked loop (PLL) allows the high-frequency bus voltage v to be controlled. H Since the q-axis component is zero, we have:

[0078]

[0079] Performing a Park transform on the high-frequency inductor current yields the dq-axis current components:

[0080]

[0081] Adding a PI controller results in:

[0082]

[0083] Design a dual closed-loop controller, with the control structure as follows: Figure 7 As shown.

[0084] The DC port control method of the high-frequency AC bus type power router of this application will be described below with reference to specific embodiments and accompanying drawings.

[0085] based on Figure 2 This paper presents a four-port high-frequency bus-type power router, where each port contains only one power submodule. Simulation verification was performed using MATLAB / Simulink software. Port 1 is a relaxation port connected to a DC power supply, while the remaining ports are power ports connected to DC loads or power sources. Simulation parameters are shown in Table 1.

[0086] Table 1 Simulation Parameters

[0087] Port 1 DC power supply voltage 650V DC voltage reference value at port 2 750V DC voltage reference value at port 3 750V DC voltage reference value at port 4 700V

[0088] The simulation timing is as follows:

[0089] (1) When t = 0s, the modular multi-active bridge starts.

[0090] (2) At t = 0.1s, port 2 switches from conventional phase-shift control to... Figure 7 The new reactive power control shown still maintains a port voltage of 750V. Ports 3 and 4 remain conventional phase-shift control.

[0091] (3) At t = 0.2s, port 3 switches from conventional phase-shift control to reactive power suppression dual closed-loop control, and the port voltage is still controlled at 750V. Port 4 remains under conventional phase-shift control.

[0092] (4) At t = 0.25s, the conventional phase shift control of port 4 is switched to reactive power suppression dual closed-loop control, and the port voltage is still controlled at 700V.

[0093] (5) At t = 0.3s, the power at port 2 changes.

[0094] (6) At t = 0.4s, the power at port 3 changes.

[0095] (7) At t = 0.45s, the power at port 4 changes.

[0096] Simulation results are as follows Figures 8 to 14 As shown. The DC port control method described in the above embodiment can effectively reduce the reactive power of each port.

[0097] The DC port control method for a high-frequency AC bus-type power router proposed in this application utilizes high-frequency bus information and high-frequency inductor current information to calculate the DC port voltage and control the DC port, effectively reducing the reactive power of each port. This avoids the problem of significant current stress generated within the modular multi-active bridge and substantial reactive power transmission between ports, which leads to a decrease in system efficiency when the voltage conversion ratios of different ports differ under single-phase-shift control.

[0098] Next, referring to the accompanying drawings, a DC port control device for a high-frequency AC bus-type power router according to an embodiment of this application is described.

[0099] Figure 15 This is an example diagram of a DC port control device for a high-frequency AC bus-type power router according to an embodiment of this application.

[0100] A high-frequency AC bus-type power router includes multiple power sub-modules connected via a high-frequency bus. These power sub-modules are cascaded or connected in parallel to form multiple DC ports with different voltage and power levels, such as... Figure 15 As shown, the DC port control device includes: a modulation module 100, a sampling module 200, and a control module 300.

[0101] The modulation module 100 modulates multiple DC ports using a 50% duty cycle phase-shift modulation method, with the switching signals of the power semiconductor devices in the upper and lower arms of the full-bridge DC port being mutually inverted. The sampling module 200 samples the high-frequency bus voltage and current, treating the high-frequency bus as a square wave source to simplify the topology of the multiple DC ports, and establishes a loop voltage equation relating the high-frequency bus voltage, high-frequency inductor current, and high-frequency inductance for the simplified DC ports. The control module 300 transforms the loop voltage equation to remove high-frequency components, adds a phase-locked loop, sets the q-axis component of the high-frequency bus voltage to 0, obtains the d-axis component of the high-frequency bus voltage, performs a Park transformation on the high-frequency inductor current to obtain the dq-axis current component of the high-frequency inductor current, and adds PI control to the d-axis component of the high-frequency bus voltage and the dq-axis current component of the high-frequency inductor current to obtain the dq-axis voltage component of the DC port.

[0102] Optionally, in one embodiment of this application, the high-frequency bus voltage is the sum of the AC output voltages of each DC port.

[0103] Optionally, in one embodiment of this application, the high-frequency bus voltage is:

[0104]

[0105] Among them, v sk The three-level AC voltage output from port k to the high-frequency bus side, l k V is the inductance coefficient of port k, N is the number of DC ports, and V is the inductance coefficient of port k. k ω is the stable DC voltage value at port k. s Let α be the switching angular frequency. k β is the inner phase shift angle of the DC port k. k The outward phase shift angle of the DC port k.

[0106] Optionally, in one embodiment of this application, the loop voltage equation establishing the relationship between the high-frequency bus voltage, high-frequency bus current, and high-frequency inductance for the simplified DC port is as follows:

[0107]

[0108] Among them, V dc For the port DC voltage, α s ω is the inner phase shift angle of the DC port. s β is the switching angular frequency. s V is the outward phase shift angle of the DC port. H β represents the fundamental amplitude of the high-frequency bus voltage. H The fundamental phase of the high-frequency bus voltage, p is the differential operator, L is the inductance, and I is the voltage. L β is the fundamental amplitude of the inductor current.L This is the phase of the fundamental frequency of the inductor current.

[0109] Optionally, in one embodiment of this application, the dq-axis voltage components of the DC port are:

[0110]

[0111] Among them, i Ld i is the d-axis component of the inductor current. Lq v is the q-axis component of the inductor current. Hd v represents the d-axis component of the fundamental amplitude of the high-frequency bus voltage. Hq K represents the q-axis component of the fundamental amplitude of the high-frequency bus voltage. p K is the proportional coefficient of the current PI controller. i is the integral coefficient of the current PI controller.

[0112] It should be noted that the explanation of the aforementioned embodiment of the DC port control method for a high-frequency AC bus type power router also applies to the DC port control device of the high-frequency AC bus type power router in this embodiment, and will not be repeated here.

[0113] The DC port control device of the high-frequency AC bus-type power router proposed in this application calculates the DC port voltage using high-frequency bus information and high-frequency inductor current information, and controls the DC port to effectively reduce the reactive power of each port. This avoids the problem of large current stress generated inside the modular multi-active bridge and a large amount of reactive power transmission between ports, which leads to a decrease in system efficiency when the voltage conversion ratios of each port are different under single-phase-shift control.

[0114] Figure 16 A schematic diagram of the structure of an electronic device provided in an embodiment of this application. The electronic device may include:

[0115] The memory 1601, the processor 1602, and the computer program stored on the memory 1601 and executable on the processor 1602.

[0116] When the processor 1602 executes the program, it implements the DC port control method of the high-frequency AC bus type power router provided in the above embodiments.

[0117] Furthermore, electronic devices also include:

[0118] Communication interface 1603 is used for communication between memory 1601 and processor 1602.

[0119] The memory 1601 is used to store computer programs that can run on the processor 1602.

[0120] The memory 1601 may include high-speed RAM memory, and may also include non-volatile memory, such as at least one disk storage device.

[0121] If the memory 1601, processor 1602, and communication interface 1603 are implemented independently, then the communication interface 1603, memory 1601, and processor 1602 can be interconnected via a bus to complete communication between them. The bus can be an Industry Standard Architecture (ISA) bus, a Peripheral Component Interconnect (PCI) bus, or an Extended Industry Standard Architecture (EISA) bus, etc. Buses can be categorized as address buses, data buses, control buses, etc. For ease of representation, Figure 16 The bus is represented by a single thick line, but this does not mean that there is only one bus or one type of bus.

[0122] Optionally, in a specific implementation, if the memory 1601, processor 1602, and communication interface 1603 are integrated on a single chip, then the memory 1601, processor 1602, and communication interface 1603 can communicate with each other through an internal interface.

[0123] The processor 1602 may be a central processing unit (CPU), an application specific integrated circuit (ASIC), or one or more integrated circuits configured to implement the embodiments of this application.

[0124] This embodiment also provides a computer-readable storage medium storing a computer program, characterized in that, when the program is executed by a processor, it implements the DC port control method of the high-frequency AC bus-type power router as described above.

[0125] In the description of this specification, the references to terms such as "one embodiment," "some embodiments," "example," "specific example," or "some examples," etc., indicate that a specific feature, structure, material, or characteristic described in connection with that embodiment or example is included in at least one embodiment or example of this application. In this specification, the illustrative expressions of the above terms do not necessarily refer to the same embodiment or example. Furthermore, the specific features, structures, materials, or characteristics described may be combined in any suitable manner in one or more embodiments or examples. Moreover, without contradiction, those skilled in the art can combine and integrate the different embodiments or examples described in this specification, as well as the features of different embodiments or examples.

[0126] Furthermore, the terms "first" and "second" are used for descriptive purposes only and should not be construed as indicating or implying relative importance or implicitly specifying the number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include at least one of that feature. In the description of this application, "N" means at least two, such as two, three, etc., unless otherwise explicitly specified.

[0127] Any process or method described in the flowchart or otherwise herein can be understood as representing a module, segment, or portion of code comprising one or more N executable instructions for implementing custom logic functions or processes, and the scope of the preferred embodiments of this application includes additional implementations in which functions may be performed not in the order shown or discussed, including substantially simultaneously or in reverse order depending on the functions involved, as should be understood by those skilled in the art to which embodiments of this application pertain.

[0128] It should be understood that the various parts of this application can be implemented using hardware, software, firmware, or a combination thereof. In the above embodiments, the N steps or methods can be implemented using software or firmware stored in memory and executed by a suitable instruction execution system. For example, if implemented in hardware as in another embodiment, it can be implemented using any one or a combination of the following techniques known in the art: discrete logic circuits having logic gates for implementing logical functions on data signals, application-specific integrated circuits (ASICs) having suitable combinational logic gates, programmable gate arrays (PGAs), field-programmable gate arrays (FPGAs), etc.

[0129] Those skilled in the art will understand that all or part of the steps of the methods in the above embodiments can be implemented by a program instructing related hardware. The program can be stored in a computer-readable storage medium, and when executed, the program includes one or a combination of the steps of the method embodiments.

Claims

1. A DC port control method for a high-frequency AC bus-type power router, characterized in that, The high-frequency AC bus-type power router includes multiple power sub-modules connected via a high-frequency bus. These power sub-modules are cascaded or connected in parallel to form multiple DC ports with multiple voltage and power levels. The DC port control method includes the following steps: The multiple DC ports are modulated using a phase-shift modulation method with a 50% duty cycle, and the switching signals of the power semiconductor devices in the upper and lower bridge arms of the full bridge of the DC ports are mutually inverted. The high-frequency bus voltage and high-frequency bus current are sampled, the high-frequency bus is regarded as a square wave source, the topology of the multiple DC ports is simplified, and the loop voltage equation of the relationship between the high-frequency bus voltage, high-frequency inductor current and high-frequency inductor is established for the simplified DC ports. After transforming the loop voltage equation to remove high-frequency components, and adding a phase-locked loop, the high-frequency bus voltage is adjusted. q The axis component is 0, thus obtaining the high-frequency bus voltage. d The axis component is used to perform a Park transform on the high-frequency inductor current to obtain the high-frequency inductor current. dq The d-axis current component, in the context of the high-frequency bus voltage d-axis component and the high-frequency inductor current... dq By incorporating PI control into the shaft current component, the DC port's... dq The axis voltage component, where, The high-frequency bus voltage is: in, For port k The three-level AC voltage output to the high-frequency bus side, For port k The inductance coefficient, where N is the number of DC ports. For port k DC voltage stability value, ω s The switching angular frequency, DC port k The inward phase angle, DC port k The outward phase angle; The loop voltage equations relating the high-frequency bus voltage, the high-frequency bus current, and the high-frequency inductance established for the simplified DC port are as follows: in, The port DC voltage. The internal phase shift angle of the DC port. The switching angular frequency, The outward phase shift angle of the DC port. V H This represents the fundamental amplitude of the high-frequency bus voltage. β H This is the fundamental phase of the high-frequency bus voltage. p For differential operators, For inductance, This represents the fundamental amplitude of the inductor current. This is the phase of the fundamental frequency of the inductor current.

2. The method according to claim 1, characterized in that, The high-frequency bus voltage is the sum of the AC output voltages of each DC port.

3. The method according to claim 1, characterized in that, The DC port dq The axis voltage component is: in, Inductor current d Axial components, Inductor current q Axial components, The fundamental amplitude of the high-frequency bus voltage d Axial components, The fundamental amplitude of the high-frequency bus voltage q Axial components, The proportional gain of the current PI controller. is the integral coefficient of the current PI controller.

4. A DC port control device for a high-frequency AC bus type power router, characterized in that, The high-frequency AC bus-type power router includes multiple power sub-modules connected via a high-frequency bus. These power sub-modules are cascaded or connected in parallel to form multiple DC ports with multiple voltage and power levels. The DC port control device includes: The modulation module is used to modulate the multiple DC ports using a phase-shift modulation method with a 50% duty cycle, and the switching signals of the power semiconductor devices in the upper and lower bridge arms of the full bridge of the DC ports are mutually inverted. The sampling module is used to sample the high-frequency bus voltage and high-frequency bus current, treat the high-frequency bus as a square wave source, simplify the topology of the multiple DC ports, and establish the loop voltage equation for the relationship between the high-frequency bus voltage, high-frequency inductor current and high-frequency inductor for the simplified DC ports. The control module is used to transform the loop voltage equation to remove high-frequency components and add a phase-locked loop to control the high-frequency bus voltage. q With the d-axis component set to 0, the d-axis component of the high-frequency bus voltage is obtained. A Park transform is then performed on the high-frequency inductor current to obtain the high-frequency inductor current. dq The shaft current component, in the high-frequency bus voltage d The axial component and the high-frequency inductor current dq By incorporating PI control into the shaft current component, the DC port's... dq The axis voltage component, where, The high-frequency bus voltage is: in, For port k The three-level AC voltage output to the high-frequency bus side, For port k The inductance coefficient, where N is the number of DC ports. For port k DC voltage stability value, ω s The switching angular frequency, DC port k The inward phase angle, DC port k The outward phase angle; The loop voltage equations relating the high-frequency bus voltage, the high-frequency bus current, and the high-frequency inductance established for the simplified DC port are as follows: in, The port DC voltage. The internal phase shift angle of the DC port. The switching angular frequency, The outward phase shift angle of the DC port. V H This represents the fundamental amplitude of the high-frequency bus voltage. β H This is the fundamental phase of the high-frequency bus voltage. p For differential operators, For inductance, This represents the fundamental amplitude of the inductor current. This is the phase of the fundamental frequency of the inductor current.

5. The apparatus according to claim 4, characterized in that, The high-frequency bus voltage is the sum of the AC output voltages of each DC port.

6. An electronic device, characterized in that, include: The device includes a memory, a processor, and a computer program stored in the memory and executable on the processor, wherein the processor executes the program to implement the DC port control method of the high-frequency AC bus-type power router as described in any one of claims 1-3.

7. A computer-readable storage medium having a computer program stored thereon, characterized in that, The program is executed by the processor to implement the DC port control method of the high-frequency AC bus type power router as described in any one of claims 1-3.

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