Signal design methods and devices

Abstract

This application provides a signal design method and apparatus that enables signals used for target sensing to have a large anti-Doppler range. The method includes: solving an optimization problem to obtain a product sequence. The optimization problem is based on constraints and maximizing an objective function. The constraints limit the sidelobes of the mutual ambiguity functions of a first signal and a second signal to be less than or equal to a first threshold within the anti-Doppler frequency shift range. The objective function is composed of the norms of the variables, and the product sequence is the solution of the variables in the optimization problem. The product sequence is used to determine the first signal and the second signal, which are used to sense the target object.

Description

[0001] This application claims priority to Chinese Patent Application No. 202210010261.6, filed with the State Intellectual Property Office of China on January 26, 2022, entitled "A Waveform Transmission and Reception Method", the entire contents of which are incorporated herein by reference. Technical Field

[0002] This application relates to the field of communications, and more particularly to signal design methods and apparatus. Background Technology

[0003] Golay complementary pairs (GCPs) are a class of sequences with perfect aperiodic autocorrelation properties. Based on this, GCPs are often used as sensing sequences to measure the distance to sensing targets.

[0004] During ranging, the sensing device generates a sensing signal based on the Global Collision Protocol (GCP) and transmits it to the target. This sensing signal is reflected by the target, producing an echo signal. Essentially, the echo signal is the same as the sensing signal, only delayed by the propagation time from the sensing device to the target. Since the sensing signal also possesses perfect aperiodic autocorrelation, the sensing device, upon receiving the echo signal, can perform an aperiodic autocorrelation operation between the echo signal and the sensing signal, and determine the target's position based on the result.

[0005] However, the perfect aperiodic autocorrelation property of the sensing signal generated based on GCP can only be maintained at 0 Doppler. When ranging a moving sensing target, the echo signal contains a Doppler frequency shift caused by the target's velocity, thus disrupting the perfect aperiodic autocorrelation property. Besides the maximum correlation peak at 0 displacement, the aperiodic autocorrelation function of the sensing signal and the echo signal exhibits numerous sidelobes at other displacements.

[0006] The presence of sidelobes reduces the ranging accuracy of sensing devices. Furthermore, when a sensing device measures the range of multiple moving targets, the maximum correlation peak of a weak target may be overwhelmed by the sidelobes of a strong target, leading to target loss. Therefore, it is necessary to implement Doppler-resistant design for the sensing signal. Summary of the Invention

[0007] This application provides a signal design method and apparatus that enables the signal used for target sensing to have a large anti-Doppler range.

[0008] Firstly, a signal design method is provided, comprising: solving an optimization problem to obtain a product sequence, which is used to determine a first signal and a second signal, and the first and second signals are used to sense a target object. The optimization problem is derived based on constraints and maximizing an objective function. The constraints limit the sidelobes of the mutual ambiguity functions of the first and second signals to be less than or equal to a first threshold within the anti-Doppler frequency shift interval. The objective function is composed of the norms of the variables, and the product sequence represents the solution of the variables in the optimization problem.

[0009] Based on this scheme, the sensing device solves an optimization problem with the objective function as the goal and the anti-Doppler frequency shift interval and sidelobe suppression level as constraints, obtaining a product sequence. This product sequence ensures that the sidelobes of the CAF of the first and second signals, determined by the product sequence, remain low within a large anti-Doppler frequency shift interval. In other words, it enables the signal used for target sensing to have a large anti-Doppler interval, thereby improving ranging performance.

[0010] In one possible design, the objective function is used to indicate the power ratio of the echo signal to the noise signal after cross-correlation calculation of the second signal. In other words, the objective function can indicate the signal-to-noise ratio (SNR) at the receiver.

[0011] Based on this possible design, since the optimization problem aims to maximize the SNR at the receiver, the design of this application can also achieve a high SNR gain at the receiver. In other words, the scheme of this application achieves a high SNR gain at the receiver while maintaining a large anti-Doppler frequency shift range.

[0012] In one possible design, the optimization problem is:

[0013]

[0014] Where ||z||1 represents the 1-norm of the variable z. Let |z||² represent the square of the 1-norm of the variable z, and |z||² represent the 2-norm of the variable z. Let E represent the square of the 2-norm of variable z, where δ is the first threshold. s Let E be an N×N dimensional matrix, where N is the length of the product sequence. s Determined by the anti-Doppler frequency shift interval, ||E s z||2 indicates the energy magnitude of the sidelobes of the mutually ambiguous function.

[0015] In one possible design, matrix E s The element in the m-th row and n-th column is:

[0016]

[0017] Where, θ D This is used to indicate the anti-Doppler frequency shift interval in radians. The anti-Doppler frequency shift interval in radians is determined by the anti-Doppler frequency shift interval in Hertz, which is determined by f. D instruct.

[0018] In one possible design, the length of the product sequence is 16, and the sidelobe threshold of the mutual ambiguity function is 10. -3 When the size of the anti-Doppler frequency shift interval is π, the product sequence is:

[0019] 2.3374e-04-4.5702e-03j,

[0020] 2.7275e-02+2.6275e-03j,

[0021] -1.2932e-02+8.2504e-02j,

[0022] -1.6627e-01-3.9741e-02j,

[0023] 8.7385e-02-2.4902e-01j,

[0024] 2.9747e-01+1.4686e-01j,

[0025] -1.9503e-01+3.0688e-01j,

[0026] -3.0555e-01-2.0732e-01j,

[0027] 1.7558e-01-3.2128e-01j,

[0028] 3.4648e-01+1.1512e-01j,

[0029] -5.3800e-02+3.4359e-01j,

[0030] -2.8593e-01-1.2917e-02j,

[0031] -3.6182e-03-1.8776e-01j,

[0032] 9.1405e-02-5.0281e-03j,

[0033] 2.1849e-03+2.9660e-02j,

[0034] -4.8841e-03+3.9983e-04j;

[0035] Where e+0x or e-0x is scientific notation, and e+01 represents ×10 1 e-01 represents ×10 -1 .

[0036] In one possible design, the product sequence is used to determine the first signal and the second signal, comprising: the product sequence is used to determine the first sequence and the second sequence, the product sequence being the Hadamard product of the first sequence and the second sequence; the first sequence and the Gray complement pair GCP are used to determine the first signal, and the first sequence, the second sequence, and the GCP are used to determine the second signal.

[0037] In one possible design, the second sequence is a sequence in a second sequence set, and the first sequence is the sequence in the first sequence set corresponding to the second sequence. The Hadamard product of a sequence in the second sequence set and its corresponding sequence in the first sequence set is a product sequence. The absolute value of the sum of all elements of the second sequence is the maximum value among a plurality of values, which includes the absolute value of the sum of all elements of each sequence in the second sequence set.

[0038] In one possible design, the lengths of the first and second sequences are 16, and the first threshold is 10. -3 When the size of the anti-Doppler frequency shift interval is π,

[0039] The first sequence is: 1,1,-1,-1,1,1,-1,-1,-1,1,1,-1,-1,-1,1,-1,-1;

[0040] The second sequence is:

[0041] 2.3374e-04-4.5702e-03j,

[0042] 2.7275e-02+2.6275e-03j,

[0043] 1.2932e-02-8.2504e-02j,

[0044] 1.6627e-01+3.9741e-02j,

[0045] 8.7385e-02-2.4902e-01j,

[0046] 2.9747e-01+1.4686e-01j,

[0047] 1.9503e-01-3.0688e-01j,

[0048] 3.0555e-01+2.0732e-01j,

[0049] 1.7558e-01-3.2128e-01j,

[0050] 3.4648e-01+1.1512e-01j,

[0051] 5.3800e-02-3.4359e-01j,

[0052] 2.8593e-01+1.2917e-02j,

[0053] -3.6182e-03-1.8776e-01j,

[0054] 9.1405e-02-5.0281e-03j,

[0055] -2.1849e-03-2.9660e-02j,

[0056] 4.8841e-03-3.9983e-04j;

[0057] Where e+0x or e-0x is scientific notation, and e+01 represents ×10 1 e-01 represents ×10 -1 .

[0058] In one possible design, the real parts of all elements in the second sequence have the same sign; or, the imaginary parts of all elements in the second sequence have the same sign.

[0059] In one possible design, the real parts of all elements in the second sequence are positive, and the lengths of both the first and second sequences are 16, with a first threshold of 10. -3 When the size of the anti-Doppler frequency shift interval is π:

[0060] The first sequence is: 1,1,-1,-1,1,1,-1,-1,-1,1,1,-1,-1,-1,1,1,-1;

[0061] The second sequence is:

[0062] 2.3374e-04-4.5702e-03j,

[0063] 2.7275e-02+2.6275e-03j,

[0064] 1.2932e-02-8.2504e-02j,

[0065] 1.6627e-01+3.9741e-02j,

[0066] 8.7385e-02-2.4902e-01j,

[0067] 2.9747e-01+1.4686e-01j,

[0068] 1.9503e-01-3.0688e-01j,

[0069] 3.0555e-01+2.0732e-01j,

[0070] 1.7558e-01-3.2128e-01j,

[0071] 3.4648e-01+1.1512e-01j,

[0072] 5.3800e-02-3.4359e-01j,

[0073] 2.8593e-01+1.2917e-02j,

[0074] 3.6182e-03+1.8776e-01j,

[0075] 9.1405e-02-5.0281e-03j,

[0076] 2.1849e-03+2.9660e-02j,

[0077] 4.8841e-03-3.9983e-04j;

[0078] Where e+0x or e-0x is scientific notation, and e+01 represents ×10 1 e-01 represents ×10 -1 .

[0079] In one possible design, the imaginary part of all elements in the second sequence is positive, and the lengths of the first and second sequences are both 16, with a first threshold of 10. -3 When the size of the anti-Doppler frequency shift interval is π:

[0080] The first sequence is: -1,1,1,-1,-1,1,1,-1,-1,1,1,-1,-1,-1,-1,1,1;

[0081] The second sequence is:

[0082] -2.3374e-04+4.5702e-03j,

[0083] 2.7275e-02+2.6275e-03j,

[0084] -1.2932e-02+8.2504e-02j,

[0085] 1.6627e-01+3.9741e-02j,

[0086] -8.7385e-02+2.4902e-01j,

[0087] 2.9747e-01+1.4686e-01j,

[0088] -1.9503e-01+3.0688e-01j,

[0089] 3.0555e-01+2.0732e-01j,

[0090] -1.7558e-01+3.2128e-01j,

[0091] 3.4648e-01+1.1512e-01j,

[0092] -5.3800e-02+3.4359e-01j,

[0093] 2.8593e-01+1.2917e-02j,

[0094] 3.6182e-03+1.8776e-01j,

[0095] -9.1405e-02+5.0281e-03j,

[0096] 2.1849e-03+2.9660e-02j,

[0097] -4.8841e-03+3.9983e-04j;

[0098] Where e+0x or e-0x is scientific notation, and e+01 represents ×10 1 e-01 represents ×10 -1 .

[0099] In one possible design, the first signal comprises sub-signals within N periods, where N is the length of the first sequence; the first sequence and GCP are used to determine the first signal, including: the nth element of the first sequence determines a sequence in the GCP, which is used to generate the sub-signals within the nth period of the first signal, where n = 0, 1, ... N-1.

[0100] In one possible design, the GCP sequence includes an x ​​sequence and a y sequence, and the first signal, the first sequence, and the GCP satisfy the following formula:

[0101]

[0102] Among them, s P (t) is the first signal, P[n] is the nth element of the first sequence, x(t-nT) or y(t-nT) is the sub-signal within the nth period of the first signal, the x sequence is used to generate x(t-nT), the y sequence is used to generate y(t-nT), and T is the period of the sub-signal of the first signal.

[0103] In one possible design, the first signal comprises sub-signals within N periods, and the second signal comprises sub-signals within N periods, where N is the length of the first sequence and the second sequence.

[0104] In one possible design, when the anti-Doppler frequency shift interval is [0, θ] D When the second signal is in the nth period, the sub-signal is the product of the conjugate of the nth element of the second sequence and the sub-signal in the nth period of the first signal, n = 0, 1, ... N-1.

[0105] In one possible design, when the anti-Doppler frequency shift interval is [0, θ] D When the GCP sequence includes the x sequence and the y sequence, the second signal, the first sequence, the second sequence, and the GCP satisfy the following formula:

[0106]

[0107] Among them, s Q (t) is the second signal, Q * [n] is the conjugate of the nth element Q[n] of the second sequence, P[n] is the nth element of the first sequence, x(t-nT) or y(t-nT) is the sub-signal within the nth period of the first signal, the x sequence is used to generate x(t-nT), the y sequence is used to generate y(t-nT), and T is the period of the sub-signal of the first signal.

[0108] In one possible design, when the anti-Doppler frequency shift interval is [-θ] D When n = 0, the sub-signal in the nth period of the second signal is the product of the nth element of the second sequence and the sub-signal in the nth period of the first signal, n = 0, 1, ... N-1.

[0109] In one possible design, when the anti-Doppler frequency shift interval is [-θ] D When [0, 0], the GCP sequence includes the x sequence and the y sequence, and the second signal, the first sequence, the second sequence, and the GCP satisfy the following formula:

[0110]

[0111] Among them, s Q (t) is the second signal, Q[n] is the nth element of the second sequence, P[n] is the nth element of the first sequence, x(t-nT) or y(t-nT) is the sub-signal within the nth period of the first signal, the x sequence is used to generate x(t-nT), the y sequence is used to generate y(t-nT), and T is the period of the sub-signal of the first signal.

[0112] In one possible design, the method further includes: sending a first signal and receiving an echo signal of the first signal; performing an aperiodic cross-correlation operation based on the echo signal and a second signal; and determining the distance to the target object based on the result of the aperiodic cross-correlation operation.

[0113] In one possible design, the first signal is either a single-carrier signal or a multi-carrier signal. Based on this possible design, using a single-carrier or multi-carrier signal as the first signal can adapt to various communication scenarios, enabling the solution of this application to be widely used.

[0114] It should be noted that the aforementioned first aspect and any possible design schemes can be executed by a sensing device, or by components of the sensing device, such as a processor, chip, or chip system, or by a logic module or software capable of implementing all or part of the functions of the sensing device. Alternatively, it can be executed by any electronic device, or by components of that electronic device, such as a processor, chip, or chip system, or by a logic module or software capable of implementing all or part of the functions of the electronic device. This application does not impose specific limitations in this regard.

[0115] Secondly, a communication device is provided for implementing the various methods described above. This communication device can be a sensing device, or a device contained within a sensing device, such as a chip. The communication device includes modules, units, or means corresponding to the methods described above. These modules, units, or means can be implemented in hardware, software, or by hardware executing corresponding software. The hardware or software includes one or more modules or units corresponding to the functions described above.

[0116] In some possible designs, the communication device may include a processing module. Furthermore, the communication device may also include a transceiver module. This transceiver module, also referred to as a transceiver unit, is used to implement the transmission and / or reception functions in any of the above aspects and any possible implementations. The transceiver module may consist of transceiver circuits, transceivers, transceivers, or communication interfaces. The processing module can be used to implement the processing functions in any of the above aspects and any possible implementations.

[0117] In some possible designs, the transceiver module includes a sending module and a receiving module, which are used to implement the sending and receiving functions in any of the above aspects and any possible implementation methods.

[0118] Thirdly, a communication device is provided, comprising: a processor and a memory; the memory is used to store computer instructions, which, when executed by the processor, cause the communication device to perform the method described in any of the preceding aspects. The communication device may be a sensing device, or a device included in the aforementioned sensing device, such as a chip.

[0119] Fourthly, a communication device is provided, comprising: a processor and a communication interface; the communication interface being used to communicate with a module outside the communication device; the processor being used to execute computer programs or instructions to cause the communication device to perform the methods described in any of the preceding aspects. The communication device may be a sensing device, or a device included in the aforementioned sensing device, such as a chip.

[0120] Fifthly, a communication device is provided, comprising: an interface circuit and a processor. The interface circuit is a code / data read / write interface circuit, used to receive computer execution instructions (which are stored in memory and may be read directly from memory or may be transmitted through other devices) and transmit them to the processor. The processor is used to execute the computer execution instructions to cause the communication device to perform the methods described in any of the preceding aspects. The communication device may be a sensing device, or a device included in the aforementioned sensing device, such as a chip.

[0121] A sixth aspect provides a communication device, comprising: at least one processor; the processor being configured to execute a computer program or instructions to cause the communication device to perform the method described in any of the preceding aspects. The communication device may be a sensing device, or a device included in the aforementioned sensing device, such as a chip.

[0122] In some possible designs, the communication device includes a memory for storing necessary program instructions and data. This memory may be coupled to the processor, or it may be independent of the processor.

[0123] In some possible designs, the communication device can be a chip or a chip system. When the device is a chip system, it can be composed of chips or may include chips and other discrete components.

[0124] In a seventh aspect, a computer-readable storage medium is provided that stores instructions which, when executed on a communication device, cause the communication device to perform the method described in any of the preceding aspects.

[0125] Eighthly, a computer program product containing instructions is provided, which, when run on a communication device, enables the communication device to perform the method described in any of the preceding aspects.

[0126] It is understood that when the communication device provided by any of the second to eighth aspects is a chip, the aforementioned sending action / function can be understood as output information, and the aforementioned receiving action / function can be understood as input information.

[0127] The technical effects of any of the design methods in aspects two through eight can be found in the technical effects of the different design methods in aspect one above, and will not be repeated here. Attached Figure Description

[0128] Figure 1 A simulation diagram of a self-fuzzy function for a GCP-based pulse train signal provided in an embodiment of this application;

[0129] Figure 2 A schematic diagram of a radar sensing scene provided in an embodiment of this application;

[0130] Figure 3 A simulation diagram illustrating the loss of weak targets in a radar sensing scenario, provided as an embodiment of this application;

[0131] Figure 4 A schematic diagram illustrating a communication scenario provided in an embodiment of this application;

[0132] Figure 5a This application provides a schematic diagram of a perception system in a smart home scenario.

[0133] Figure 5b This application provides a schematic diagram of perception in a vehicle-to-everything (V2X) scenario.

[0134] Figure 6a This is a schematic diagram of the structure of a communication device provided in an embodiment of this application;

[0135] Figure 6b This is a schematic diagram of another communication device provided in an embodiment of this application;

[0136] Figure 6c This is a schematic diagram of the structure of another communication device provided in the embodiments of this application;

[0137] Figure 7 A schematic flowchart illustrating a signal design method provided in an embodiment of this application;

[0138] Figure 8 A flowchart illustrating a sensing method provided in an embodiment of this application;

[0139] Figure 9 A waveform diagram of a single carrier provided for an embodiment of this application;

[0140] Figure 10a A simulation diagram of the CAF corresponding to the PTM scheme provided in the embodiments of this application;

[0141] Figure 10b A simulation diagram of the CAF corresponding to the BD scheme provided in the embodiments of this application;

[0142] Figure 10c A simulation diagram of the mutual ambiguity function CAF corresponding to the NS scheme provided in the embodiments of this application;

[0143] Figure 10d The sequence length provided in this embodiment is 16, θ D A CAF simulation diagram when π / 3;

[0144] Figure 10e The sequence length provided in this embodiment is 16, θ D A CAF simulation diagram when = 2π / 3;

[0145] Figure 10f The sequence length provided in this embodiment is 16, θ D A schematic diagram of CAF simulation when π = π;

[0146] Figure 11 A schematic diagram illustrating the generation process of a multi-carrier waveform provided in an embodiment of this application;

[0147] Figure 12 A schematic diagram illustrating resource allocation as provided in an embodiment of this application;

[0148] Figure 13a A simulation diagram of the CAF corresponding to the PTM scheme when the sequence length is 32, as provided in the embodiments of this application;

[0149] Figure 13b A simulation diagram of the CAF corresponding to the BD scheme when the sequence length is 32, provided for an embodiment of this application;

[0150] Figure 13c A simulation diagram of the CAF corresponding to the NS scheme when the sequence length is 32, provided for the embodiments of this application;

[0151] Figure 13d The sequence length provided in this embodiment is 32, θ D A CAF simulation diagram when π / 3;

[0152] Figure 13e The sequence length provided in this embodiment is 32, θ DA CAF simulation diagram when = 2π / 3;

[0153] Figure 13f The sequence length provided in this embodiment is 32, θ D A schematic diagram of CAF simulation when π = π;

[0154] Figure 14 This is a schematic diagram of the structure of a communication device provided in an embodiment of this application. Detailed Implementation

[0155] In the description of this application, unless otherwise stated, " / " indicates that the objects before and after are in an "or" relationship. For example, A / B can mean A or B. "And / or" in this application is merely a description of the relationship between the related objects, indicating that there can be three relationships. For example, A and / or B can mean: A exists alone, A and B exist simultaneously, and B exists alone. A and B can be singular or plural.

[0156] In the description of this application, unless otherwise stated, "multiple" means two or more. "At least one of the following" or similar expressions refer to any combination of these items, including any combination of a single item or a plurality of items. For example, at least one of a, b, or c can mean: a, b, c, ab, ac, bc, or abc, where a, b, and c can be single or multiple.

[0157] Furthermore, to facilitate a clear description of the technical solutions in the embodiments of this application, the terms "first" and "second" are used in the embodiments of this application to distinguish identical or similar items with substantially the same function and effect. Those skilled in the art will understand that the terms "first" and "second" do not limit the quantity or execution order, and the terms "first" and "second" are not necessarily different.

[0158] In the embodiments of this application, the terms "exemplary" or "for example" are used to indicate that something is an example, illustration, or description. Any embodiment or design that is described as "exemplary" or "for example" in the embodiments of this application should not be construed as being more preferred or advantageous than other embodiments or design. Specifically, the use of terms such as "exemplary" or "for example" is intended to present the relevant concepts in a specific manner to facilitate understanding.

[0159] It is understood that the term "embodiment" used throughout the specification means that a specific feature, structure, or characteristic related to an embodiment is included in at least one embodiment of this application. Therefore, various embodiments throughout the specification do not necessarily refer to the same embodiment. Furthermore, these specific features, structures, or characteristics can be combined in any suitable manner in one or more embodiments. It is understood that in the various embodiments of this application, the sequence number of each process does not imply the order of execution; the execution order of each process should be determined by its function and internal logic, and should not constitute any limitation on the implementation process of the embodiments of this application.

[0160] It is understood that some optional features in the embodiments of this application can be implemented independently in certain scenarios without relying on other features, such as the current solution on which they are based, to solve the corresponding technical problems and achieve the corresponding effects. Alternatively, they can be combined with other features as needed in certain scenarios. Correspondingly, the apparatus given in the embodiments of this application can also implement these features or functions, which will not be elaborated here.

[0161] In this application, unless otherwise specified, the same or similar parts between the various embodiments can be referred to each other. In the various embodiments of this application, unless otherwise specified or logically conflicting, the terminology and / or descriptions between different embodiments are consistent and can be mutually referenced. Technical features in different embodiments can be combined to form new embodiments based on their inherent logical relationships. The following descriptions of the embodiments of this application do not constitute a limitation on the scope of protection of this application.

[0162] To facilitate understanding of the technical solutions of the embodiments of this application, a brief introduction to the relevant technologies of this application is given below.

[0163] 1) L1 norm and L2 norm:

[0164] The 1-norm of a sequence is the sum of the absolute values ​​of its elements. The 2-norm of a sequence is the square root of the sum of the squares of its elements.

[0165] For example, for a sequence a of length L, the 1 norm can be expressed as: The 2-norm can be expressed as:

[0166] 2) Correlation operation: Correlation operation refers to multiplying corresponding elements of two sequences and then adding them together. For example, for sequences a = [a1, a2, a3] and b = [b1, b2, b3], the correlation operation between them is: a1 × b1 + a2 × b2 + a3 × b3.

[0167] 3) Autocorrelation: If two sequences are identical, then the correlation operation between them is called autocorrelation.

[0168] 4) Cross-correlation: If two sequences are different, then the correlation operation between them is called cross-correlation.

[0169] 5) Aperiodic autocorrelation: When calculating the autocorrelation of sequences, the correlation value of overlapping elements in two sequences is calculated through the relative displacement between the sequences. If the sequence length is L, then the relative displacement between the sequences may have 2L-1 possible cases: -L+1, -L+2, ..., -1, 0, 1, ..., L-2, L-1. Therefore, the aperiodic autocorrelation calculation has a total of 2L-1 possible results.

[0170] For example, for the sequence [1,2,3], when the relative displacement between sequences is -2, the following situation applies:

[0171] 1, 2, 3

[0172] 1, 2, 3

[0173] At this point, the aperiodic autocorrelation result is 1×3=3.

[0174] When the relative displacement between sequences is -1, the following situation applies:

[0175] 1, 2, 3

[0176] 1, 2, 3

[0177] At this point, the aperiodic autocorrelation result is 1×2+2×3=8. Similarly, when the relative shifts between sequences are -2, -1, 0, 1, 2, the aperiodic autocorrelation results are 3, 8, 14, 8, 3 respectively.

[0178] 6) Aperiodic cross-correlation: When calculating the cross-correlation of sequences, the correlation value of overlapping elements in two sequences is calculated by the relative shift between the sequences.

[0179] 7) Perfect aperiodic autocorrelation: If the aperiodic autocorrelation result of a sequence is zero at every shift except 0, then the sequence has perfect aperiodic autocorrelation. If the values ​​at shifts other than 0 are not zero, but are very small compared to the peak value at 0, then the sequence has good aperiodic autocorrelation.

[0180] 8) Perfect aperiodic cross-correlation: If the aperiodic cross-correlation result of two sequences is 0 at all shifts, then the two sequences have perfect aperiodic cross-correlation, or they are said to be orthogonal to each other. If the aperiodic cross-correlation result of two sequences remains small at all shifts, then the two sequences have good aperiodic cross-correlation.

[0181] 9) Golay complementary pair (GCP):

[0182] GCP, also known as Gray complement sequence or GCP sequence, is a class of perfect aperiodic autocorrelation sequences. It is defined as follows: for a pair of sequences x and y of code length L, if the sum of their aperiodic autocorrelation function (AACF) is zero everywhere except at the zero shift, then these two sequences are a pair of GCPs. Specifically, for the sequence x = [x[0], x[1], ..., x[N-1]], its AACF is defined as:

[0183]

[0184] Where k represents displacement, and k = 0 represents zero displacement. The AACF (denoted as C) of sequence y. y [k]) is similar to the AACF of sequence x, see C. x The description of [k] will not be repeated here.

[0185] For example, for sequences x = [1,1,1,-1] and y = [1,1,-1,1], since the AACF of sequence x is C x [k] = [-1, 0, 1, 4, 1, 0, -1], k = -3, -2, ..., 3, and the AACF of sequence y is C. y [k] = [1,0,-1,4,-1,0,1], k = -3,-2,..,3, since C x [k]+C y [k] = [0,0,0,8,0,0,0], therefore sequences x and y are a pair of GCPs.

[0186] Because GCPs possess perfect aperiodic autocorrelation, they are often used as sensing sequences. Sensing devices (such as radar) can generate pulse train signals (as sensing signals) based on GCPs, with the general form s(t) = x(t) + y(tT). Here, x(t) and y(tT) represent the pulse train signals generated from the x and y sequences based on the GCP, respectively, and T represents the pulse repetition interval (PRI) of s(t). The general forms of x(t) and y(t) can be expressed as:

[0187]

[0188]

[0189] Where g(t) represents the pulse signal, T CThis represents the duration of the pulse signal. It is understandable that s(t) also possesses perfect aperiodic autocorrelation, and therefore can be used for ranging of sensed targets.

[0190] During ranging, the sensing device sends a signal s(t) to the target, which is then transmitted back to the target, generating an echo signal s(t-τ). Essentially, the echo signal is the same as the sensing signal, except that it is delayed by the propagation delay τ caused by the distance from the sensing device to the target. Therefore, if a non-periodic autocorrelation operation is performed on the echo signal and the sensing signal, the maximum correlation peak will be obtained at the time point corresponding to the propagation delay τ. The sensing device can then determine the echo delay by searching for the delay corresponding to the maximum correlation peak, and thus determine the location of the target.

[0191] However, the perfect aperiodic autocorrelation property of the sensing signal generated based on GCP is only maintained at 0 Doppler. When ranging a moving sensing target, the perfect aperiodic autocorrelation property of the sensing signal is destroyed. At this time, in addition to the maximum correlation peak at 0 displacement, the aperiodic autocorrelation function of the sensing signal and the echo signal also has a large number of sidelobes at other displacements.

[0192] As one implementation, the auto ambiguity function (AAF) can be used to study the influence of Doppler on the aperiodic autocorrelation function of the sensed signal. For the signal s(t), its AAF is defined as:

[0193]

[0194] Where τ represents the time delay, f represents the Doppler frequency shift, and s * (t) represents the conjugate of signal s(t). As shown above, the self-ambiguity function is essentially a non-periodic autocorrelation function that considers different Doppler frequency shifts.

[0195] For example, when using a GCP of length 64 and a rectangular window pulse to generate a pulse train signal for sensing, the AAF results of s(t) under different Doppler frequency shifts are as follows: Figure 1 As shown. See also Figure 1 The x-axis represents the Doppler frequency shift, the y-axis represents the time delay, and the z-axis represents the AAF result. According to... Figure 1 It can be seen that although the AAF of s(t) can still reach its maximum value at 0 time delay, a large number of side lobes appear at other time delays due to the existence of Doppler frequency shift, and the side lobes also increase with the increase of Doppler frequency shift.

[0196] The presence of sidelobes can lead to two problems: First, ranging accuracy decreases when ranging high-speed moving targets. Second, when ranging multiple moving targets, the different distances and radar cross-sections (RCS) of the targets result in significant energy differences in their echo signals. In this case, the maximum correlation peak of a weak target may be overwhelmed by the sidelobes of a strong target, causing target loss (a phenomenon known as the "near-far effect" in radar).

[0197] For example, such as Figure 2 As shown, assume the radar simultaneously ranges two moving targets. Target 1 has a larger RCS area and is closer to the radar, and can be considered a strong target. Target 2 has a smaller RCS area and is farther from the radar, and can be considered a weak target. Since the energy of the echo signal reflected by the strong target is much greater than that of the echo signal reflected by the weak target, the aperiodic autocorrelation function of the sensing signal and the echo signal will exhibit the following... Figure 3 This is the situation shown. In this case, the maximum correlation peak of the weak target is completely submerged by the sidelobes of the strong target, resulting in the loss of the weak target.

[0198] To address the aforementioned issues, it is necessary to implement Doppler-resistant design for the sensing signal, ensuring that the AAF sidelobes of the sensing signal remain at a very low level within a sufficiently large Doppler range.

[0199] Currently, Doppler resistance is mainly achieved through a joint design of transmitted and local signals. In this joint design approach, the transmitting end of the sensing device transmits a burst signal x(t) or y(t) generated by the GCP sequence x and y in each of the N PRIs.

[0200] Specifically, whether x(t) or y(t) is transmitted within a certain PRI is controlled by the sequence P = [P[0], P[1], ..., P[N-1]]. Each element of sequence P takes a value of 1 or -1, and the general form of the transmitted signal is as follows:

[0201]

[0202] In other words, in the nth PRI, if P[n] = 1, then x(t) is sent; if P[n] = -1, then y(t) is sent.

[0203] At the receiving end of the sensing device, s is no longer used. P Instead of performing aperiodic autocorrelation calculations on (t) and the echo signal, a local signal s generated based on the sequence Q = [Q[0], Q[1], ..., Q[N-1]] is used. Q(t) is cross-correlated with the echo signal using aperiodic methods.

[0204] When the anti-Doppler interval is a positive interval, the general form of the local signal is:

[0205]

[0206] In other words, within the nth PRI, the local signal is obtained by multiplying the transmitted signal by the conjugate of Q[n].

[0207] Furthermore, the cross ambiguity function (CAF) can be used to study the influence of Doppler frequency shift on the aperiodic cross-correlation function of the local signal and the echo signal. The cross ambiguity function essentially considers the aperiodic cross-correlation function with different Doppler frequency shifts, and its specific form is similar to that of the AAF, the difference being that the two signals used in the CAF operation are different signals. Refer to the relevant description of AAF; it will not be repeated here.

[0208] In calculating s P (t) and s Q When (t) is in CAF mode, since the pulse signal does not affect s P (t) and s Q The CAF of (t) is such that it can be ignored and s can be calculated. P (t) and s Q CAF of (t). At this point, the simplified s P (t) and s Q The CAF of (t) can be expressed in the following form:

[0209]

[0210] In the above expression, the first term represents the maximum correlation peak at 0 delay, and the second term represents the sidelobes at other delays. Based on this, the sidelobes (i.e., the second term in the above expression) can be reduced to a very low level by designing P-sequences and Q-sequences.

[0211] When designing transmitted and local signals using P-sequences and Q-sequences, the Q-sequence also affects the signal-to-noise ratio (SNR) at the receiving end of the sensing device. For example, under non-ideal channel conditions, the received signal may include both echo and noise signals, or in other words, the echo signal may be accompanied by noise. In this case, the echo signal is the useful signal. It should be noted that in this application, SNR can also be referred to as SNR gain, and the two terms are interchangeable.

[0212] In this scenario, when the power of the noise signal is constant, s is used.Q (t) After processing the received signal (e.g., performing CAF operation), the noise power is entirely determined by the Q sequence, while the power of the useful signal is determined by s. P (t) and s Q The CAF value of (t) is determined at k=0, f=0. For example, assuming the power of the noise signal before processing is N0, then after s... Q (t) After receiving and processing, the power of the noise signal is Where L represents the length of the GCP sequence. Let ||Q|| be the 2-norm of the Q-sequence, which is the square of ||Q||2. Correspondingly, after s... Q (t) After receiving and processing, the power of the useful signal is in The power of the useful signal before processing is determined by the transmission power of the sensing device and the RCS area of ​​the sensing target. Let |Q|| be the square of the 1-norm of the Q sequence. In summary, after s... Q After processing (t), the SNR gain at the receiver is exist Given a time, the SNR gain is determined solely by The decision has been made. In existing research, there are three main design schemes for the P and Q sequences:

[0213] 1) Prouhet-thue-morse (PTM) scheme.

[0214] In the PTM scheme, the P sequence is a PTM sequence of length N, and the Q sequence is a sequence of all 1s of length N. It should be noted that the PTM sequence of length N is uniquely determined.

[0215] 2) Binomial design (BD) scheme.

[0216] In the BD scheme, the P sequence is an alternating ±1 sequence of length N, and the Q sequence is a binomial sequence of length N, i.e.

[0217] 3) Null space (NS) scheme.

[0218] In the NS scheme, the sequence [P[0]Q[0],P[1]Q[1],...,P[N-1]Q[N-1]] is required to be the null basis vector of matrix E. Where:

[0219]

[0220] After determining the null space basis vectors [z[0], z[1], ..., z[N-1]] of matrix E, if the real part of z[n] is greater than 0, then P[n] = 1; otherwise, P[n] = -1. Correspondingly, if P[n] = 1, then Q[n] = z[n]; if P[n] = -1, then Q[n] = -z[n].

[0221] For example, as shown in Tables 1 and 2 below, the P-sequence and Q-sequence corresponding to the PTM scheme, BD scheme, and NS scheme are shown when N equals 16 and 32, respectively.

[0222] Table 1

[0223]

[0224]

[0225] In this embodiment, e+0x or e-0x represents scientific notation; for example, e+01 represents ×10⁻¹⁰. 1 e-01 represents ×10 -1 e+02 means ×10 2 It is hereby stated that the following embodiments will not be described in detail.

[0226] Table 2

[0227]

[0228]

[0229] However, when using the P-sequence and Q-sequence corresponding to the PTM scheme to design the transmitted and local signals, the anti-Doppler interval is too small to meet the ranging requirements for high-speed moving targets. When using the P-sequence and Q-sequence corresponding to the BD and NS schemes to design the transmitted and local signals, the SNR gain at the receiver is low.

[0230] Based on this, this application provides a signal design method that, through the design of the P-sequence and Q-sequence, enables the transmitted signal and the local signal to have a large anti-Doppler range. Furthermore, this results in a higher SNR gain at the receiver.

[0231] The technical solutions of this application embodiment can be used in various communication systems, including 3GPP communication systems such as 5G or 6G mobile communication systems, vehicle-to-everything (V2X) systems, device-to-device (D2D) communication systems, machine-to-machine (M2M) communication systems, Internet of Things (IoT) systems, and other next-generation communication systems. The communication system can also be a non-3GPP communication system, such as Wi-Fi or other wireless local area network (WLAN) systems; there is no limitation.

[0232] The technical solutions of this application embodiment can be applied to various communication scenarios, such as one or more of the following communication scenarios: smart home, D2D, V2X, and IoT communication scenarios.

[0233] The communication systems and scenarios applicable to this application mentioned above are merely illustrative examples, and are not limited to these examples. This will be explained uniformly here and will not be repeated below.

[0234] See Figure 4 This application provides a communication scenario. In this scenario, a sensing device sends a sensing signal. After the sensing signal is reflected by at least one stationary or moving target object (also referred to as the sensing target), the sensing device can receive the echo signal of the sensing signal, thereby enabling the sensing device to sense the target object. Figure 1 The scenario described is merely an example and is not actually limited to one sensing device interacting with one or more target objects. For instance, multiple sensing devices can interact with the same target object.

[0235] Optionally, the sensing device in this application can be a terminal device with radar functionality or a network device. The terminal device can be a device with wireless transceiver capabilities. The network device is a device that connects the terminal device to a wireless network.

[0236] The network equipment may be a next-generation node B (gNodeB or gNB) in a 5th generation (5G) system or a 6th generation (6G) system; or it may be a transmission reception point (TRP); or it may be a base station in a future public land mobile network (PLMN). This application embodiment does not specifically limit this.

[0237] Terminal equipment can also be referred to as user equipment (UE), terminal, access terminal, user unit, user station, mobile station (MS), remote station, remote terminal, mobile terminal (MT), user terminal, wireless communication equipment, user agent, or user device, etc. Terminal equipment can be, for example, a wireless terminal in IoT, V2X, D2D, M2M, 5G network, 6G network, or a future PLMN. Terminal equipment can be deployed on land, including indoors or outdoors, handheld or vehicle-mounted; it can also be deployed on water (such as on ships); and it can also be deployed in the air (such as on airplanes, balloons, and satellites).

[0238] For example, terminal devices can be drones, IoT devices (e.g., sensors, electricity meters, water meters, etc.), V2X devices, stations (STs) in wireless local area networks (WLANs), cellular phones, cordless phones, session initiation protocol (SIP) phones, wireless local loop (WLL) stations, personal digital assistant (PDA) devices, handheld devices with wireless communication capabilities, computing devices or other processing devices connected to a wireless modem, in-vehicle devices, wearable devices (also known as wearable smart devices), tablets or computers with wireless transceiver capabilities, virtual reality (VR) terminals, terminals in industrial control, terminals in self-driving, terminals in remote medical care, terminals in smart grids, terminals in transportation safety, and terminals in smart cities. Terminals in cities, terminals in smart homes, vehicle terminals, vehicles with vehicle-to-vehicle (V2V) communication capabilities, intelligent connected vehicles, drones with drone-to-drone (UAV-to-UAV (U2U)) communication capabilities, etc.

[0239] For example, in a smart home scenario, such as Figure 5a As shown, sensing devices can be various smart appliances in the home, such as smart TVs and smart speakers. When it is necessary to track a person's trajectory, each terminal in the home can send sensing signals to detect the person, thereby enhancing the accuracy of trajectory tracking. Alternatively, in a V2X scenario, such as... Figure 5b As shown, the sensing device can be an in-vehicle terminal, which can send sensing signals and receive the echo signals of the sensing signals reflected by the target object to sense the surrounding road conditions, etc.

[0240] The related functions of the sensing device involved in this application can be implemented by one device, or by multiple devices, or by one or more functional modules within one device, or by one or more chips, or by a system on a chip (SOC) or chip system. A chip system can be composed of chips or include chips and other discrete devices. The embodiments of this application do not specifically limit this.

[0241] It is understood that the above functions can be network elements in hardware devices, software functions running on dedicated hardware, a combination of hardware and software, or virtualization functions instantiated on a platform (e.g., a cloud platform).

[0242] For example, the relevant functions of the sensing device involved in this application can be achieved through... Figure 6a This is achieved through the communication device 600. Figure 6a The diagram shown is a structural schematic of a communication device 600 provided in an embodiment of this application. The communication device 600 includes one or more processors 601 and at least one communication interface. Figure 6a (This is merely an example illustration of a communication interface 604 and a processor 601. Optionally, it may also include a communication line 602 and a memory 603.)

[0243] The processor 601 may be a general-purpose central processing unit (CPU), a microprocessor, an application-specific integrated circuit (ASIC), or one or more integrated circuits used to control the execution of the program of the present application.

[0244] In a specific implementation, as one embodiment, the processor 601 may include one or more CPUs, for example... Figure 6a CPU0 and CPU1 in the CPU.

[0245] In a specific implementation, as one embodiment, the communication device 600 may include multiple processors. Each of these processors may be a single-core processor or a multi-core processor. The processors here may include, but are not limited to, at least one of the following: a central processing unit (CPU), a microprocessor, a digital signal processor (DSP), a microcontroller unit (MCU), or an artificial intelligence processor, and other computing devices that run software. Each computing device may include one or more cores for executing software instructions to perform calculations or processing.

[0246] The communication line 602 can be used for communication between different components included in the communication device 600.

[0247] The communication interface 604 can be used to communicate with other devices or communication networks, such as Ethernet, wireless access networks (RAN), and wireless local area networks (WLAN). The communication interface 604 can be a transceiver or similar device, or it can be an input / output interface. Alternatively, the communication interface 604 can also be a transceiver circuit located within the processor 601, used to implement signal input and signal output for the processor.

[0248] The memory 603 can be a device with storage functionality. For example, it can be read-only memory (ROM) or other types of static storage devices capable of storing static information and instructions; random access memory (RAM) or other types of dynamic storage devices capable of storing information and instructions; electrically erasable programmable read-only memory (EEPROM); compact disc read-only memory (CD-ROM) or other optical disc storage; optical disc storage (including compressed optical discs, laser discs, optical discs, digital universal optical discs, Blu-ray discs, etc.); magnetic disk storage media or other magnetic storage devices; or any other medium capable of carrying or storing desired program code in the form of instructions or data structures and accessible by a computer, but not limited thereto. The memory can exist independently and be connected to the processor via communication line 602. The memory can also be integrated with the processor.

[0249] The memory 603 stores computer execution instructions for implementing the scheme of this application, and its execution is controlled by the processor 601. The processor 601 executes the computer execution instructions stored in the memory 603 to implement the method provided in the embodiments of this application.

[0250] Alternatively, in this embodiment, the processor 601 may execute the processing-related functions of the method provided in the following embodiments of this application, and the communication interface 604 may be responsible for communicating with other devices or communication networks. This embodiment does not specifically limit this.

[0251] Optionally, the computer execution instructions in the embodiments of this application may also be referred to as application code, and the embodiments of this application do not specifically limit this.

[0252] In a specific implementation, as one embodiment, the communication device 600 may further include an output device 605 and an input device 606. The output device 605 communicates with the processor 601 and can display information in various ways. For example, the output device 605 may be a liquid crystal display (LCD), a light-emitting diode (LED) display device, a cathode ray tube (CRT) display device, or a projector, etc. The input device 606 communicates with the processor 601 and can receive user input in various ways. For example, the input device 606 may be a mouse, keyboard, touchscreen device, or sensing device, etc.

[0253] Taking the 604 communication interface as a transceiver as an example, such as Figure 6b The diagram shown is a structural schematic of another communication device 600 provided in an embodiment of this application. The communication device 600 includes a processor 601 and a transceiver 604. The communication device 600 can be a sensing device, or a chip therein. Figure 6b Only the main components of the communication device 600 are shown. In addition to the processor 601 and transceiver 604, the communication device may further include a memory 603 and input / output devices (not shown).

[0254] The processor 601 is primarily used to process communication protocols and data, control the entire communication device, execute software programs, and process the data from those programs. The memory 603 is primarily used to store software programs and data. The transceiver 604 may include radio frequency (RF) circuitry and an antenna. The RF circuitry is primarily used for converting baseband signals to RF signals and processing RF signals. The antenna is primarily used for transmitting and receiving RF signals in the form of electromagnetic waves.

[0255] The processor 601, transceiver 604, and memory 603 can be connected via a communication bus.

[0256] When the communication device is powered on, the processor 601 can read the software program in the memory 603, interpret and execute the instructions of the software program, and process the data of the software program. When data needs to be transmitted wirelessly, the processor 601 performs baseband processing on the data to be transmitted and outputs the baseband signal to the radio frequency (RF) circuit. The RF circuit then performs RF processing on the baseband signal and transmits the RF signal outward in the form of electromagnetic waves through the antenna. When data is sent to the communication device, the RF circuit receives the RF signal through the antenna, converts the RF signal into a baseband signal, and outputs the baseband signal to the processor 601. The processor 601 converts the baseband signal into data and processes the data.

[0257] In another implementation, the radio frequency circuitry and antenna can be set up independently of the processor performing baseband processing. For example, in a distributed scenario, the radio frequency circuitry and antenna can be arranged remotely, independent of the communication device.

[0258] For example, such as Figure 6c As shown, Figure 6b The processor 601 may include a digital signal processor, a signal generator, and an analog-to-digital converter. The radio frequency circuitry for signal transmission may include an up-converter and a power amplifier, and the radio frequency circuitry for signal reception may include a down-converter and a power amplifier. The antenna may include a transmitting antenna and a receiving antenna.

[0259] As one possible implementation, a signal generator can be used to generate the signal. Up-converters and down-converters are used to modulate the signal onto a high-frequency carrier and demodulate the signal from the high-frequency carrier, respectively. A power amplifier is used to amplify the power of the signal. An analog-to-digital converter is used to convert digital signals to analog signals. A digital signal processor is used to generate the sensing sequence and perform aperiodic autocorrelation and / or aperiodic cross-correlation operations.

[0260] It should be noted that, Figure 6a or Figure 6b or Figure 6c The structural composition shown does not constitute a limitation on the communication device, except... Figure 6a or Figure 6b or Figure 6c In addition to the components shown, the communication device may include more or fewer components than illustrated, or combine certain components, or have different component arrangements. The illustrated components may be implemented in hardware, software, or a combination of software and hardware.

[0261] The method provided in this application will now be described in detail with reference to the accompanying drawings. In the embodiments of this application, the executing entity may perform some or all of the steps in the embodiments of this application. These steps or operations are merely examples, and the embodiments of this application may also perform other operations or variations thereof. Furthermore, the steps may be performed in different orders as presented in the embodiments of this application, and it is not necessary to perform all the operations in the embodiments of this application.

[0262] like Figure 7 The diagram illustrates a signal design method provided in this application. This method can be executed by a sensing device or any electronic device; this application does not specifically limit its execution. See also... Figure 7 Taking the method executed by a sensing device as an example, the method includes the following steps:

[0263] S701. Solve the optimization problem to obtain the product sequence.

[0264] The optimization problem is derived from constraints and maximizing the objective function. The objective function is composed of the norms of the variables, and the product sequence represents the solution of the variables in this optimization problem. The product sequence is used to determine the first and second signals, which are then used to perceive the target object.

[0265] For example, the first signal can be a sensing signal, and the second signal can be a local signal. The local signal is used to perform an aperiodic cross-correlation operation with the echo signal of the sensing signal to sense the target object. The constraint condition is used to limit the sidelobes of the mutual ambiguity function of the first and second signals to be less than or equal to a first threshold within the anti-Doppler frequency shift interval.

[0266] Optionally, the objective function is used to indicate the power ratio of the echo signal to the noise signal after cross-correlation calculation of the second signal. In other words, the objective function can indicate the signal-to-noise ratio (SNR) at the receiver.

[0267] As one possible implementation, the optimization problem can be expressed as:

[0268]

[0269] Where ||z||1 represents the 1-norm of the variable z. Let |z||² represent the square of the 1-norm of the variable z. Let ||z||² represent the 2-norm of the variable z. Let δ represent the square of the 2-norm of the variable z. δ is the first threshold. E s Let N be an N×N dimensional matrix, where N is the length of the product sequence.

[0270] Wherein, matrix E s It can be determined by the anti-Doppler frequency shift interval. ||E s z||2 indicates the energy magnitude of the sidelobe of the mutual ambiguity function of the first and second signals.

[0271] For example, matrix E s The element in the m-th row and n-th column can be:

[0272]

[0273] Where, θ D Used to indicate the anti-Doppler frequency shift interval in radians. For example, the anti-Doppler interval in radians is [-θ]. D ,θ D Let n = 0, 1, ..., N-1. m = 0, 1, ..., K, where K is a positive integer less than or equal to N-1.

[0274] For example, the anti-Doppler frequency shift interval in radians can be determined by the anti-Doppler frequency shift interval in Hertz, and the anti-Doppler frequency shift interval in Hertz can be determined by f D Indication. For example, the anti-Doppler interval in Hertz is [-f D ,f D ]. θ D and f D It can satisfy: θ D =2πf D T, then the anti-Doppler frequency shift interval in radians can be [-2πf D T,2πf D [T] Wherein, T is the period of the sub-signals included in the first signal. For example, when the first signal is a pulse train signal, T can be the PRI of the pulse train signal. The sub-signals included in the first signal will be described in subsequent embodiments and will not be repeated here.

[0275] Understandable, matrix E s The element in the m-th row and n-th column can also have other forms, which are not specifically limited in this application.

[0276] Optionally, in practical applications, the first threshold and the anti-Doppler interval can be flexibly adjusted according to actual needs, thereby improving the applicability of the solution in this application.

[0277] Optionally, the product sequence used to determine the first signal and the second signal may include: a product sequence used to determine the first sequence and the second sequence. Wherein, the product sequence is the Hadamard product of the first sequence and the second sequence. Further, the first sequence and the Gray complement pair (GCP) are used to determine the first signal, and the first sequence, the second sequence, and the GCP are used to determine the second signal.

[0278] Optionally, when step S701 is performed by the sensing device, the sensing device may continue to perform steps S702 and S703 to determine the first signal and the second signal. When step S701 is performed by another electronic device, the electronic device may send the product sequence to the sensing device after obtaining it. After receiving the product sequence from the electronic device, the sensing device may continue to perform steps S702 and S703; or, after obtaining the product sequence, the electronic device may further determine the first sequence and the second sequence and send them to the sensing device. After receiving the first sequence and the second sequence from the electronic device, the sensing device may continue to perform step S703.

[0279] S702. Determine the first sequence and the second sequence based on the product sequence.

[0280] For example, the first sequence can be a P sequence and the second sequence can be a Q sequence. Therefore, the relationship between the product sequence, the first sequence, and the second sequence can be expressed as: z[n] = P[n]Q[n].

[0281] Understandably, since the product sequence is the Hadamard product of the first and second sequences, the product sequence, the first sequence, and the second sequence have the same length. In this embodiment, N represents this length.

[0282] S703. Determine a first signal based on a first sequence and a GCP, and determine a second signal based on the first sequence, a second sequence, and the GCP sequence.

[0283] Optionally, the first signal may include sub-signals within N periods, or in other words, the first signal includes N sub-signals, which are periodic signals. For example, when the first signal is a pulse train signal, the sub-signals of the first signal may be pulse signals.

[0284] Optionally, when the first signal includes sub-signals within N periods, the sensing device determines the first signal based on the first sequence and the GCP sequence. This may include: the sensing device determining a sequence of sub-signals within the nth period of the GCP used to generate the first signal based on the nth element of the first sequence, where n = 0, 1, ..., N-1. In the following embodiments of this application, the GCP including an x ​​sequence and a y sequence is used as an example for illustration.

[0285] In other words, the sub-signals within the nth period of the first signal are generated from a sequence in the GCP. Whether this sequence is the x sequence or the y sequence in the GCP is determined by the nth element of the first sequence.

[0286] For example, when the nth element of the first sequence is equal to 1, the sub-signal within the nth period of the first signal can be generated by the x sequence in the GCP; when the nth element of the first sequence is equal to -1, the sub-signal within the nth period of the first signal can be generated by the y sequence in the GCP. Therefore, the first signal, the first sequence, and the GCP can satisfy the following formula:

[0287]

[0288] Among them, s P (t) is the first signal. P[n] is the nth element of the first sequence. x(t-nT) or y(t-nT) is the sub-signal within the nth period of the first signal. The x sequence is used to generate x(t-nT), and the y sequence is used to generate y(t-nT). T is the period of the sub-signal of the first signal. For example, when the first signal is a pulse train signal and the sub-signal is a pulse signal, T can be PRI.

[0289] Optionally, the second signal may include sub-signals within N periods, or in other words, the second signal includes N sub-signals, which are periodic signals. The periods of the sub-signals included in the second signal and the periods of the sub-signals included in the first signal may be the same.

[0290] For example, when the anti-Doppler frequency shift interval is a positive interval, such as [0, θ] D The sub-signal within the nth period of the second signal can be the product of the conjugate of the nth element of the second sequence and the sub-signal within the nth period of the first signal. When the anti-Doppler interval is a negative interval, for example [-θ D [,0], the sub-signal in the nth period of the second signal can be the product of the nth element of the second sequence and the sub-signal in the nth period of the first signal, n=0,1,...N-1.

[0291] For example, when the anti-Doppler frequency shift interval is a positive interval, the second signal, the first sequence, the second sequence, and the GCP can satisfy the following formula:

[0292]

[0293] When the anti-Doppler frequency shift interval is negative, the second signal, the first sequence, the second sequence, and the GCP can satisfy the following formula:

[0294]

[0295] Among them, s Q (t) represents the second signal. Q[n] represents the nth element of the second sequence. * [n] is the conjugate of the nth element Q[n] of the second sequence. P[n] is the nth element of the first sequence. x(t-nT) or y(t-nT) is a sub-signal of the first signal. The x sequence is used to generate x(t-nT), and the y sequence is used to generate y(t-nT). T is the period of the sub-signal of the first signal.

[0296] in, It can represent the sub-signal within the nth period of the second signal when the anti-Doppler frequency shift interval is a positive interval. It can represent the sub-signal within the nth period of the second signal when the anti-Doppler frequency shift interval is negative.

[0297] Based on the scheme of this application, the sensing device is constructed with the goal of maximizing the SNR at the receiver. An optimization problem is established with constraints of the anti-Doppler frequency shift range and the sidelobe suppression level. Solving this optimization problem yields a product sequence. Then, a first sequence and a second sequence are determined based on the product sequence, ensuring that the energy of the CAF sidelobes of the transmitted signal and the local signal generated based on the first and second sequences remains low within a large anti-Doppler frequency shift range. Furthermore, since the optimization problem aims to maximize the SNR at the receiver, the design of this application also achieves a high SNR gain at the receiver. In other words, the scheme of this application achieves both a large anti-Doppler frequency shift range and a high SNR gain at the receiver.

[0298] The solutions (i.e., product sequences) to the above optimization problem are explained below for different first thresholds, anti-Doppler frequency shift intervals, and sequence lengths. Table 3 shows the product sequences for three combinations of first thresholds and anti-Doppler intervals when the sequence length N is equal to 8, 12, 16, 20, 24, 28, and 32.

[0299] Table 3

[0300]

[0301]

[0302]

[0303]

[0304]

[0305] Understandably, if the Hadamard product of two sequences equals any of the product sequences shown in Table 3, then both sequences fall within the protection scope of this application.

[0306] Furthermore, given the product sequence as shown in Table 3, this application can further restrict the first and second sequences.

[0307] As one possible implementation, the second sequence can be a sequence in a second sequence set, and the first sequence is the sequence in the first sequence set corresponding to the second sequence. For example, the second sequence set and the first sequence set can include all sequence combinations that satisfy all product sequences shown in Table 3. There is a one-to-one correspondence between the sequences in the second sequence set and the first sequence set, and the Hadamard product of a sequence in the second sequence set and its corresponding sequence in the first sequence set is a product sequence.

[0308] The absolute value of the sum of all elements in the second sequence is the maximum value among a plurality of values, which includes the absolute value of the sum of all elements in each sequence in the set of second sequences.

[0309] For example, suppose the first set of sequences includes sequences A, B, and C, and the second set of sequences includes sequences D, E, and F. If the absolute value of the sum of all elements of sequence D... The absolute value of the sum of all elements in sequence E, where 1 is the numerical value. The absolute value of the sum of all elements in sequence F, where 2 is the numerical value. If the value is 3, and the value 2 is the maximum value among the values ​​1, 2, and 3, then the second sequence is sequence E.

[0310] Correspondingly, if the sequences in the first sequence set and the sequences in the second sequence set correspond one-to-one in order, then when the second sequence is sequence E, the first sequence is sequence A.

[0311] For example, in this possible implementation, the values ​​of the first sequence and the second sequence can be as shown in Tables 4 and 5. Here, the P sequence represents the first sequence, and the Q sequence represents the second sequence.

[0312] Table 4

[0313]

[0314]

[0315]

[0316]

[0317]

[0318] Table 5

[0319]

[0320]

[0321]

[0322]

[0323] As another possible implementation, the real parts of all elements in the second sequence have the same sign. Alternatively, the imaginary parts of all elements in the second sequence have the same sign.

[0324] For example, in this possible implementation, the real parts of all elements in the second sequence can be positive numbers. In this case, the values ​​of the first and second sequences can be as shown in Tables 6 and 7.

[0325] Table 6

[0326]

[0327]

[0328]

[0329]

[0330]

[0331] Table 7

[0332]

[0333]

[0334]

[0335]

[0336]

[0337] For example, in this possible implementation, the imaginary part of all elements in the second sequence can be positive. In this case, the values ​​of the first and second sequences can be as shown in Tables 8 and 9.

[0338] Table 8

[0339]

[0340]

[0341]

[0342]

[0343]

[0344] Table 9

[0345]

[0346]

[0347]

[0348]

[0349] It should be noted that the first and second sequences shown in Tables 4 to 9 above are merely exemplary descriptions of the first and second sequences in this application, and do not limit the first and second sequences of this application to be exactly as shown in Tables 4 to 9. Furthermore, although this application provides various combinations of first and second sequences, it does not limit the specific technical solution to supporting all combinations of first and second sequences defined in this application; it only requires supporting combinations of at least one first and second sequence of at least one length as defined in this application.

[0350] The following is based on Figure 7 Taking the first and second signals obtained by the method shown as examples, the sensing method provided in this application will be explained. Figure 8 As shown, the method includes:

[0351] S801, The sensing device sends the first signal.

[0352] Optionally, the first signal can be a single-carrier signal or a multi-carrier signal. In other words, the first signal can be a single-carrier waveform or a multi-carrier waveform. For example, the single-carrier waveform can be a single-carrier pulse waveform, such as a rectangular window pulse, a Gaussian pulse, or a root-raised cosine pulse; this application does not specifically limit the pulse form. The multi-carrier waveform can be a cyclic prefix orthogonal frequency division multiplexing (CP-OFDM) waveform or a discrete fourier transform spread orthogonal frequency division multiplexing (DFT-s-OFDM) waveform. Of course, other forms of single-carrier or multi-carrier waveforms are also possible; this application does not specifically limit these.

[0353] Optionally, when the first signal is a single-carrier signal, the second signal is also a single-carrier signal. When the second signal is a multi-carrier signal, the second signal is also a multi-carrier signal.

[0354] S802, The sensing device receives the echo signal of the first signal.

[0355] Optionally, when multiple target objects exist, the first signal can be reflected by multiple target objects to form multiple echo signals. In this case, the sensing device can receive a total echo signal (denoted as the first echo signal) formed by the superposition of multiple echo signals reflected by multiple target objects.

[0356] S803. The sensing device performs an aperiodic cross-correlation operation based on the echo signal and the second signal, and determines the distance to the target object based on the result of the aperiodic cross-correlation operation.

[0357] Optionally, the sensing device can sample the echo signal and the second signal, and perform an aperiodic cross-correlation operation on the two sampling results. When the first signal is reflected by multiple target objects, the echo signal is the first echo signal.

[0358] Optionally, when the first signal is reflected by a target object, the sensing device can determine the signal propagation delay between the sensing device and the target object based on the displacement corresponding to the maximum correlation peak of the aperiodic cross-correlation calculation. Then, the distance between the target object and the sensing device is determined based on this signal propagation delay. Assuming the displacement corresponding to the maximum correlation peak is l, then the delay is lT. C The distance between the target object and the sensing device is clT C / 2. Where c is the speed of light. When the first signal is a single-carrier waveform, T C Indicates the duration of the narrow pulse; when the first signal is a multi-carrier waveform, T C This indicates the duration of the sampling point after time-domain sampling of a multi-carrier signal.

[0359] Optionally, when the first signal is reflected by multiple target objects, the aperiodic cross-correlation result of the echo signal and the second signal will have multiple peaks, each corresponding to a different target object. The sensing device can determine the position of the target object corresponding to each peak based on these multiple peaks. Refer to the relevant explanations on determining distance based on the maximum correlation peak; these will not be repeated here.

[0360] Optionally, under non-ideal channel conditions, the echo signal may be accompanied by noise. That is, the signal received by the sensing device in step S802 may include noise and the echo signal of the first signal. In this case, the sensing device can treat the signal received in step S802 as a whole and perform the above step S803.

[0361] The following explanation uses the example of a first and second sequence with a length N equal to 16 and the first signal being a single-carrier signal to illustrate the generation methods of the first and second signals, as well as the CAF results of the first and second signals.

[0362] For example, such as Figure 9 As shown, the sensing device can transmit narrow pulse signals g(t) of different phases in a phase-modulated manner based on the GCP, where each narrow pulse signal corresponds to an element in a sequence (x sequence or y sequence, determined by the first sequence) in the GCP. For example, when the element in the sequence is 1, the sensing device transmits a positive narrow pulse, and when the element in the sequence is -1, the sensing device transmits a negative narrow pulse.

[0363] Assuming the first signal uses a single-carrier signal with a carrier frequency f0 = 60 GHz and a bandwidth B = 400 MHz, then the width (or duration) of the narrow pulse signal g(t) is T. C = 1 / B = 2.5 nanoseconds (ns). Therefore, for a GCP of length L, one sequence (x sequence or y sequence) is represented by a wide pulse consisting of L narrow pulses, with a duration of LT. C If L equals 64, then the width of the wide pulse signals x(t) and y(t) generated according to the x and y sequences included in GCP is 64 × 2.5 = 160 ns.

[0364] Furthermore, the sensing device can repeatedly use the x and y sequences included in the GCP to generate wide pulses, thereby forming the first signal of a single-carrier pulse waveform. The number of repetitions of the wide pulse is equal to the length N of the first sequence. Figure 9 (Only three wide pulses are shown as an example; the rest are not shown). The PRI of each wide pulse is... Figure 8 The value is represented by T. In this scenario, we will take T = 5 microseconds (μs) as an example for explanation.

[0365] For example, suppose the first sequence is as shown in Table 4, where N equals 16, θ D The P-sequence, which equals π / 3, is [1,-1,1,-1,1,-1,1,-1,1,-1,1,-1,-1,1,-1,-1,-1]. The first signal consists of 16 wide pulses (or periodic signals), with PRI (or the duration of each period) of T = 5 μs. Within each wide pulse (or period), the sequence [x(t), y(t), x(t), y(t), x(t), y(t), x(t), y(t), x(t), y(t), x(t), y(t), y(t), x(t), y(t), y(t), x(t), y(t), y(t)] is transmitted sequentially based on the first sequence. x(t) or y(t) is generated by 64 narrow pulse signals g(t), each with a width of 2.5 ns.

[0366] Optionally, the structure of the second signal is similar to that of the first signal, except that: when the anti-Doppler frequency shift interval is [0, θ]... D When the nth wide pulse of the second signal is multiplied by the conjugate Q of the nth element of the second sequence, the nth wide pulse of the first signal can be multiplied by the conjugate Q of the nth element of the second sequence. * [n] is obtained. When the anti-Doppler interval is [-θ] D When [0, 0], the nth wide pulse of the second signal can be obtained by multiplying the nth wide pulse of the first signal by the nth element Q[n] of the second sequence. Refer to the relevant explanation of the first signal; it will not be repeated here.

[0367] Understandably, based on the P-sequence and Q-sequence provided by the PTM scheme, BD scheme, and NS scheme shown in Table 1, and the P-sequence and Q-sequence when N equals 16 in Tables 4 and 5, different first and second signals can be generated.

[0368] Optionally, after generating the first and second signals based on various combinations of P and Q sequences, the CAF of the first and second signals, as well as the SNR gain of the receiver corresponding to each combination, can be calculated separately. The formulas for calculating CAF and SNR can be found in the aforementioned explanations and will not be repeated here.

[0369] like Figures 10a to 10c The figures show the CAF results of the first and second signals generated using the P-sequence, BD-sequence, and NS-sequence methods shown in Table 1, respectively. Figures 10d to 10f As shown in Tables 4 and 5, N is equal to 16, θ D The CAF results of the first and second signals generated by the P-sequence and Q-sequence at π / 3, 2π / 3, and π, respectively.

[0370] See Figures 10a to 10f The x-axis represents the Doppler frequency shift in Hz, the y-axis represents the time delay in seconds (s), and the z-axis represents the CAF result in dB. The black area represents the frequency range where the CAF sidelobe energy is less than or equal to -60 dB.

[0371] Depend on Figure 10a It can be seen that the anti-Doppler frequency shift range corresponding to the PTM scheme is relatively small, approximately [-5, 5] kHz. Figure 10b and Figure 10c It can be seen that the anti-Doppler frequency shift ranges corresponding to the BD and NS schemes are relatively large. The anti-Doppler frequency shift range corresponding to the BD scheme is approximately [-46, 46] kHz, and the anti-Doppler frequency shift range corresponding to the NS scheme is approximately [-74, 74] kHz. Furthermore, from... Figures 10d to 10f Therefore, under different constraints on the anti-Doppler frequency shift intervals, the scheme of the present invention can also maintain a large anti-Doppler frequency shift interval. Under the constraint of the largest anti-Doppler frequency shift interval (i.e., θ...), D =2πf D When T = π, the anti-Doppler frequency shift range of the present invention is the largest.

[0372] Based on the above results, the anti-Doppler frequency shift ranges corresponding to the PTM scheme, BD scheme, NS scheme, and the scheme of this invention are shown in Table 10. Furthermore, Table 10 also shows the receiver SNR gain for each scheme.

[0373] Table 10

[0374]

[0375]

[0376] As shown in Table 10, the scheme proposed in this application has a larger anti-Doppler frequency shift range compared to the PTM scheme. Compared to the BD and NS schemes, it has a larger anti-Doppler frequency shift range and a larger receiver SNR gain.

[0377] The above explanation uses a single-carrier signal as an example for the first signal. The following explanation uses a first and second sequence with a length N equal to 32, where the first signal is a multi-carrier signal and the multi-carrier signal is a DFT-s-OFDM signal, to illustrate the generation methods of the first and second signals, as well as their CAF results.

[0378] For example, such as Figure 11 As shown, the sensing device performs a discrete fourier transform (DFT) on the x-sequence or y-sequence to be transmitted, then performs subcarrier mapping according to the resource element (RE) mapping rules, then performs an inverse fast fourier transform (IFFT) on the RE after subcarrier mapping, and finally inserts a fixed-length cyclic prefix (CP) to obtain a sub-signal of the first signal.

[0379] Optionally, when performing subcarrier mapping, assuming the GCP length L is 512, the carrier frequency is f0 = 28 GHz, the bandwidth B = 144 MHz, and the subcarrier spacing is 240 kHz, then the number of subcarriers that can be used is 144 MHz / 240 kHz = 600, thus allowing 600 subcarriers to transmit the x or y sequence. For example, the x or y sequence can be transmitted on the 512 subcarriers numbered 0 to 511, and the all-zero sequence can be transmitted on the remaining 88 subcarriers numbered 512 to 599. Of course, this application does not specifically limit the GCP length, carrier frequency, and subcarrier spacing; other values ​​are possible in actual implementation.

[0380] Optionally, in a joint communication and sensing (JCS) system, the communication system may also use DFT-s-OFDM waveforms. Therefore, to reduce interference between the sensing and communication systems, resource reuse is typically performed in a time-division or frequency-division manner. In this application, time-division multiplexing can be used, meaning that at the same time domain location, only the sensing signal from the sensing system or the communication signal from the communication system is transmitted, and the signal transmitted at that time domain location occupies the entire bandwidth configured in the frequency domain. Based on this method, the first signal can occupy the entire configured bandwidth, which means that compared to frequency-division multiplexing, the bandwidth occupied by the first signal can be increased, thereby improving the ranging resolution of the sensing system.

[0381] For example, such as Figure 12 As shown, assuming a time slot includes 14 DFT-s-OFDM symbols (i.e., time domain resources), and the first DFT-s-OFDM symbol in the time slot can be used for the sensing system, then an x ​​sequence or a y sequence can be transmitted using the first DFT-s-OFDM symbol in the time slot. The remaining 13 symbols in the time slot, excluding the first DFT-s-OFDM symbol, can be used to transmit communication data, or not to transmit data; this application does not specifically limit this.

[0382] based on Figure 12 In the example shown, when the length N of the first sequence is equal to 32, the sensing device occupies the first DFT-s-OFDM symbol in each of the 32 time slots to transmit either the x-sequence or the y-sequence. The first DFT-s-OFDM symbol in a given time slot ultimately transmits either the x-sequence or the y-sequence, determined by the first sequence. In this case, the duration of a time slot is the repetition interval of the sub-signals of the first signal, or the PRI of the first signal. For example, according to the current 5G new radio (NR) standard, the duration of a time slot is 0.0625ms, thus the repetition interval of the sub-signals of the first signal is 0.0625ms.

[0383] Optionally, when using time-division multiplexing for resource reuse, the specific multiplexing method or resource allocation method can be implemented by the transport layer or network layer protocol. For example, multiple consecutive DFT-s-OFDM symbols can be used for the sensing system, and other symbols can be used for the communication system; or, the multiple DFT-s-OFDM symbols allocated to the sensing system in a time slot can be non-consecutive. This application does not specifically limit the multiplexing method.

[0384] Optionally, the structure of the second signal is similar to that of the first signal, except that: when the anti-Doppler interval is [0, θ]... DWhen the nth sub-signal of the second signal is multiplied by the conjugate Q of the nth element of the second sequence, the nth sub-signal of the first signal can be multiplied by the conjugate Q of the nth element of the second sequence. * [n] is obtained. When the anti-Doppler interval is [-θ] D When [0, 0], the nth sub-signal of the second signal can be obtained by multiplying the nth sub-signal of the first signal by the nth element Q[n] of the second sequence. Refer to the relevant explanation of the first signal; it will not be repeated here.

[0385] Understandably, based on the P-sequence and Q-sequence provided by the PTM scheme, BD scheme, and NS scheme shown in Table 1, and the P-sequence and Q-sequence when N equals 32 in Tables 4 and 5, different first and second signals can be generated.

[0386] Optionally, after generating the first and second signals based on various combinations of P and Q sequences, the CAF of the first and second signals, as well as the SNR gain of the receiver corresponding to each combination, can be calculated respectively.

[0387] like Figures 13a to 13c The figures show the CAF results of the first and second signals generated using the P-sequence, BD-sequence, and NS-sequence methods shown in Table 1, respectively. Figures 13d to 13f As shown in Tables 4 and 5, N is equal to 32, θ D The CAF results of the first and second signals generated by the P-sequence and Q-sequence at π / 3, 2π / 3, and π, respectively.

[0388] See Figures 13a to 13f The x-axis represents the Doppler frequency shift in Hz, the y-axis represents the time delay in seconds (s), and the z-axis represents the CAF result in dB. The black area represents the frequency range where the CAF sidelobe energy is less than or equal to -60 dB.

[0389] Depend on Figure 13a It can be seen that the anti-Doppler frequency shift range corresponding to the PTM scheme is relatively small, approximately [-1, 1] kHz. From... Figure 13b and Figure 13c It can be seen that the anti-Doppler frequency shift ranges corresponding to the BD and NS schemes are relatively large. The anti-Doppler frequency shift range corresponding to the BD scheme is approximately [-5.5, 5.5] kHz, while that corresponding to the NS scheme is approximately [-6.5, 6.5] kHz. Furthermore, from... Figures 13d to 13f Therefore, under different constraints on the anti-Doppler frequency shift intervals, the scheme of the present invention can also maintain a large anti-Doppler frequency shift interval. Under the constraint of the largest anti-Doppler frequency shift interval (i.e., θ...), D =2πf DWhen T = π, the anti-Doppler frequency shift range of the present invention is the largest.

[0390] Based on the above results, the anti-Doppler frequency shift ranges corresponding to the PTM scheme, BD scheme, NS scheme, and the scheme of this invention are shown in Table 11. Furthermore, Table 11 also shows the receiver SNR gain for each scheme.

[0391] Table 11

[0392]

[0393] As shown in Table 11, the scheme proposed in this application has a larger anti-Doppler frequency shift range compared to the PTM scheme. It also has a larger receiver SNR gain compared to the BD and NS schemes, in some cases, such as 2πf. d When T = π, it also has a larger anti-Doppler frequency shift range.

[0394] In summary, the solution proposed in this application achieves a large anti-Doppler frequency shift range while enabling the receiver to have a high SNR gain.

[0395] It is understood that the methods and / or steps implemented by the sensing device in the above embodiments can also be implemented by components (e.g., processors, chips, chip systems, circuits, logic modules, or software such as chips or circuits) that can be used in the sensing device.

[0396] The above primarily describes the solutions provided in this application from the perspective of the device. Accordingly, this application also provides a communication device for implementing the various methods described above. This communication device can be a sensing device in the above method embodiments, a device containing the aforementioned sensing device, or a component that can be used with a sensing device.

[0397] It is understood that, in order to achieve the aforementioned functions, the communication device includes hardware structures and / or software modules corresponding to the execution of each function. Those skilled in the art should readily recognize that, based on the units and algorithm steps of the various examples described in conjunction with the embodiments disclosed herein, this application can be implemented in hardware or a combination of hardware and computer software. Whether a function is executed in hardware or by computer software driving hardware depends on the specific application and design constraints of the technical solution. Those skilled in the art can use different methods to implement the described functions for each specific application, but such implementation should not be considered beyond the scope of this application.

[0398] This application embodiment can divide the communication device into functional modules according to the above method embodiment. For example, each function can be divided into a separate functional module, or two or more functions can be integrated into one processing module. The integrated module can be implemented in hardware or as a software functional module. It should be noted that the module division in this application embodiment is illustrative and only represents one logical functional division. In actual implementation, there may be other division methods.

[0399] Figure 14 A schematic diagram of a communication device 140 is shown. The communication device 140 includes a processing module 1401 and a transceiver module 1402.

[0400] In some embodiments, the communication device 140 may further include a storage module. Figure 14 (Not shown in the image) is used to store program instructions and data.

[0401] In some embodiments, the transceiver module 1402, also referred to as a transceiver unit, is used to implement sending and / or receiving functions. The transceiver module 1402 may consist of a transceiver circuit, a transceiver, a transceiver unit, or a communication interface.

[0402] In some embodiments, the transceiver module 1402 may include a receiving module and a sending module, respectively used to perform the receiving and sending steps performed by the sensing device in the above method embodiments, and / or other processes used to support the technology described herein; the processing module 1401 may be used to perform the processing steps (e.g., determining, acquiring, generating, etc.) performed by the sensing device in the above method embodiments, and / or other processes used to support the technology described herein.

[0403] The processing module 1401 is used to solve an optimization problem to obtain a product sequence. The optimization problem is based on constraints and maximizing an objective function, where the objective function is composed of the norms of the variables. The product sequence represents the solution of the variables in the optimization problem. The product sequence is used to determine a first signal and a second signal, which are then used to perceive the target object. The constraints limit the sidelobes of the mutual ambiguity functions of the first and second signals to be less than or equal to a first threshold within the anti-Doppler frequency shift interval.

[0404] Optionally, the processing module 1401 is further configured to determine a first sequence and a second sequence based on the product sequence, wherein the product sequence is the Hadamard product of the first sequence and the second sequence; the processing module 1401 is further configured to determine a first signal based on the first sequence and the Gray complement pair GCP, and to determine a second signal based on the first sequence, the second sequence, and the GCP.

[0405] Optionally, the transceiver module 1402 is used to transmit a first signal; the transceiver module 1402 is also used to receive the echo signal of the first signal; the processing module 1401 is also used to perform an aperiodic cross-correlation operation based on the echo signal and the second signal; the processing module 1401 is also used to determine the distance of the target object based on the result of the aperiodic cross-correlation operation.

[0406] All relevant content of each step involved in the above method embodiments can be referenced from the functional description of the corresponding functional module, and will not be repeated here.

[0407] In this application, the communication device 140 is presented in an integrated manner, divided into various functional modules. Here, "module" may refer to an application-specific integrated circuit (ASIC), a circuit, a processor and memory that executes one or more software or firmware programs, integrated logic circuits, and / or other devices that can provide the above functions.

[0408] As one possible product form, those skilled in the art will conceive that the communication device 140 can adopt... Figure 6a The communication device 600 shown is in the form of this device.

[0409] As an example, Figure 14 The function / implementation process of the processing module 1401 can be achieved through... Figure 6a The processor 601 in the communication device 600 shown calls computer execution instructions stored in the memory 603 to implement the communication. Figure 14 The function / implementation process of the transceiver module 1402 can be obtained through Figure 6a This is achieved through the communication interface 604 in the communication device 600 shown.

[0410] As another possible product form, the communication device described in the embodiments of this application can also be implemented using one or more field programmable gate arrays (FPGAs), programmable logic devices (PLDs), controllers, state machines, gate logic, discrete hardware components, any other suitable circuits, or any combination of circuits capable of performing the various functions described throughout this application.

[0411] In some embodiments, when Figure 14When the communication device 140 is a chip or chip system, the function / implementation process of the transceiver module 1402 can be implemented through the input / output interface (or communication interface) of the chip or chip system, and the function / implementation process of the processing module 1401 can be implemented through the processor (or processing circuit) of the chip or chip system.

[0412] Since the communication device 140 provided in this embodiment can execute the above method, the technical effects it can achieve can be referred to the above method embodiment, and will not be repeated here.

[0413] In some embodiments, this application also provides a communication device, which includes a processor for implementing the methods in any of the above method embodiments.

[0414] As one possible implementation, the communication device also includes a memory. This memory stores necessary program instructions and data, and the processor can call the program code stored in the memory to instruct the communication device to execute the methods in any of the above method embodiments. Of course, the memory may also be absent from the communication device.

[0415] As another possible implementation, the communication device also includes an interface circuit, which is a code / data read / write interface circuit, used to receive computer execution instructions (which are stored in memory and may be read directly from memory or may be transmitted through other devices) and transmit them to the processor.

[0416] As another possible implementation, the communication device also includes a communication interface for communicating with modules outside the communication device.

[0417] It is understood that the communication device can be a chip or a chip system. When the communication device is a chip system, it can be composed of chips or may include chips and other discrete devices. This application does not specifically limit this.

[0418] This application also provides a computer-readable storage medium having a computer program or instructions stored thereon, which, when executed by a computer, implements the functions of any of the above-described method embodiments.

[0419] This application also provides a computer program product that, when executed by a computer, implements the functions of any of the above method embodiments.

[0420] Those skilled in the art will understand that, for the sake of convenience and brevity, the specific working processes of the systems, devices, and units described above can be referred to the corresponding processes in the foregoing method embodiments, and will not be repeated here.

[0421] It is understood that the systems, apparatuses, and methods described in this application can also be implemented in other ways. For example, the apparatus embodiments described above are merely illustrative. For instance, the division of units is only a logical functional division, and in actual implementation, there may be other division methods. For example, multiple units or components may be combined or integrated into another system, or some features may be ignored or not executed. Furthermore, the couplings or direct couplings or communication connections shown or discussed may be through some interfaces; indirect couplings or communication connections between devices or units may be electrical, mechanical, or other forms.

[0422] The units described as separate components may or may not be physically separate; that is, they may be located in one place or distributed across multiple network units. The components shown as units may or may not be physical units. Some or all of the units can be selected to achieve the purpose of this embodiment according to actual needs.

[0423] In addition, the functional units in the various embodiments of this application can be integrated into one processing unit, or each unit can exist physically separately, or two or more units can be integrated into one unit.

[0424] In the above embodiments, implementation can be achieved, in whole or in part, through software, hardware, firmware, or any combination thereof. When implemented using software programs, implementation can be, in whole or in part, in the form of a computer program product. This computer program product includes one or more computer instructions. When the computer program instructions are loaded and executed on a computer, all or part of the processes or functions described in the embodiments of this application are generated. The computer can be a general-purpose computer, a special-purpose computer, a computer network, or other programmable device. The computer instructions can be stored in a computer-readable storage medium or transmitted from one computer-readable storage medium to another. For example, the computer instructions can be transmitted from one website, computer, server, or data center to another via wired (e.g., coaxial cable, fiber optic, digital subscriber line (DSL)) or wireless (e.g., infrared, wireless, microwave, etc.) means. The computer-readable storage medium can be any available medium accessible to a computer or a data storage device containing one or more servers, data centers, etc., that can be integrated with the medium. The available medium can be a magnetic medium (e.g., floppy disk, hard disk, magnetic tape), an optical medium (e.g., DVD), or a semiconductor medium (e.g., solid-state disk (SSD)). In this embodiment, the computer may include the aforementioned apparatus.

[0425] Although this application has been described herein in conjunction with various embodiments, those skilled in the art, by reviewing the accompanying drawings, disclosure, and appended claims, will understand and implement other variations of the disclosed embodiments in carrying out the claimed application. In the claims, the word "comprising" does not exclude other components or steps, and "a" or "an" does not exclude a plurality. A single processor or other unit can implement several functions listed in the claims. While different dependent claims may recite certain measures, this does not mean that these measures cannot be combined to produce good results.

[0426] Although this application has been described in conjunction with specific features and embodiments, it is obvious that various modifications and combinations can be made thereto without departing from the spirit and scope of this application. Accordingly, this specification and drawings are merely exemplary illustrations of this application as defined by the appended claims, and are considered to cover any and all modifications, variations, combinations, or equivalents within the scope of this application. Clearly, those skilled in the art can make various alterations and modifications to this application without departing from the spirit and scope of this application. Thus, if such modifications and modifications of this application fall within the scope of the claims of this application and their equivalents, this application is also intended to include such modifications and modifications.

Claims

1. A signal design method, characterized in that, The method includes: Solving an optimization problem yields a product sequence. The optimization problem is based on constraints and a maximizing objective function. The constraints limit the sidelobes of the mutual ambiguity functions of the first and second signals to be less than or equal to a first threshold within the anti-Doppler frequency shift interval. The objective function is composed of the norms of the variables. The product sequence represents the solution of the variables in the optimization problem. The product sequence is used to determine the first and second signals, which are used to sense the target object. The optimization problem is: in, Denotes the 1-norm of the variable z. This represents the square of the 1-norm of the variable z. This represents the 2-norm of the variable z. This represents the square of the 2-norm of the variable z. For the first threshold, for A 3D matrix N The length of the product sequence, the matrix Determined by the anti-Doppler frequency shift interval, Indicates the energy magnitude of the sidelobes of the mutual ambiguity function.

2. The method according to claim 1, characterized in that, The objective function is used to indicate the power ratio of the echo signal to the noise signal of the first signal after cross-correlation calculation of the second signal.

3. The method according to claim 1 or 2, characterized in that, The matrix The element in the m-th row and n-th column is: in, This is used to indicate the anti-Doppler frequency shift interval in radians, which is determined by an anti-Doppler frequency shift interval in Hertz, which is determined by... instruct.

4. The method according to claim 1 or 2, characterized in that, The length of the product sequence is 16, and the sidelobe threshold of the mutually ambiguous function is... The size of the anti-Doppler frequency shift interval is When the product sequence is: 2.3374e-04-4.5702e-03j, 2.7275e-02+2.6275e-03j, -1.2932e-02+8.2504e-02j, -1.6627e-01-3.9741e-02j, 8.7385e-02-2.4902e-01j, 2.9747e-01+1.4686e-01j, -1.9503e-01+3.0688e-01j, -3.0555e-01-2.0732e-01j, 1.7558e-01-3.2128e-01j, 3.4648e-01+1.1512e-01j, -5.3800e-02+3.4359e-01j, -2.8593e-01-1.2917e-02j, -3.6182e-03-1.8776e-01j, 9.1405e-02-5.0281e-03j, 2.1849e-03+2.9660e-02j, -4.8841e-03+3.9983e-04j; in, e+0x or e-0x is scientific notation, and e+01 represents... e-01 indicates .

5. The method according to claim 1 or 2, characterized in that, The product sequence is used to determine the first signal and the second signal, including: The product sequence is used to determine the first sequence and the second sequence, and the product sequence is the Hadamard product of the first sequence and the second sequence. The first sequence and the Gray complement pair (GCP) are used to determine the first signal, and the first sequence, the second sequence, and the GCP are used to determine the second signal.

6. The method according to claim 5, wherein the second sequence is a sequence in a second sequence set, the first sequence is a sequence in a first sequence set corresponding to the second sequence, the Hadamard product of a sequence in the second sequence set and the corresponding sequence in the first sequence set is the product sequence; the absolute value of the sum of all elements of the second sequence is the maximum value among a plurality of values, the plurality of values ​​including the absolute value of the sum of all elements of each sequence in the second sequence set.

7. The method according to claim 6, wherein the lengths of the first sequence and the second sequence are 16, and the first threshold is... The size of the anti-Doppler frequency shift interval is hour, The first sequence is: 1,1,-1,-1,1,1,-1,-1,1,1,-1,-1,1,1,-1,-1,-1,-1; The second sequence is: 2.3374e-04-4.5702e-03j, 2.7275e-02+2.6275e-03j, 1.2932e-02-8.2504e-02j, 1.6627e-01+3.9741e-02j, 8.7385e-02-2.4902e-01j, 2.9747e-01+1.4686e-01j, 1.9503e-01-3.0688e-01j, 3.0555e-01+2.0732e-01j, 1.7558e-01-3.2128e-01j, 3.4648e-01+1.1512e-01j, 5.3800e-02-3.4359e-01j, 2.8593e-01+1.2917e-02j, -3.6182e-03-1.8776e-01j, 9.1405e-02-5.0281e-03j, -2.1849e-03-2.9660e-02j, 4.8841e-03-3.9983e-04j; Where e+0x or e-0x is scientific notation, and e+01 represents... e-01 indicates .

8. The method according to claim 5, wherein the real parts of all elements in the second sequence have the same sign; or, the imaginary parts of all elements in the second sequence have the same sign.

9. The method according to claim 8, wherein the real parts of all elements in the second sequence are positive numbers, and the lengths of the first sequence and the second sequence are 16, and the first threshold is... The size of the anti-Doppler frequency shift interval is hour: The first sequence is: 1,1,-1,-1,1,1,-1,-1,1,1,-1,-1,-1,1,1,-1; The second sequence is: 2.3374e-04-4.5702e-03j, 2.7275e-02+2.6275e-03j, 1.2932e-02-8.2504e-02j, 1.6627e-01+3.9741e-02j, 8.7385e-02-2.4902e-01j, 2.9747e-01+1.4686e-01j, 1.9503e-01-3.0688e-01j, 3.0555e-01+2.0732e-01j, 1.7558e-01-3.2128e-01j, 3.4648e-01+1.1512e-01j, 5.3800e-02-3.4359e-01j, 2.8593e-01+1.2917e-02j, 3.6182e-03+1.8776e-01j, 9.1405e-02-5.0281e-03j, 2.1849e-03+2.9660e-02j, 4.8841e-03-3.9983e-04j; Where e+0x or e-0x is scientific notation, and e+01 represents... e-01 indicates .

10. The method according to claim 8, wherein the imaginary part of all elements in the second sequence is positive, and the lengths of the first sequence and the second sequence are 16, and the first threshold is... The size of the anti-Doppler frequency shift interval is hour: The first sequence is: -1,1,1,-1,-1,1,1,-1,-1,1,1,-1,-1,-1,1,1; The second sequence is: -2.3374e-04+4.5702e-03j, 2.7275e-02+2.6275e-03j, -1.2932e-02+8.2504e-02j, 1.6627e-01+3.9741e-02j, -8.7385e-02+2.4902e-01j, 2.9747e-01+1.4686e-01j, -1.9503e-01+3.0688e-01j, 3.0555e-01+2.0732e-01j, -1.7558e-01+3.2128e-01j, 3.4648e-01+1.1512e-01j, -5.3800e-02+3.4359e-01j, 2.8593e-01+1.2917e-02j, 3.6182e-03+1.8776e-01j, -9.1405e-02+5.0281e-03j, 2.1849e-03+2.9660e-02j, -4.8841e-03+3.9983e-04j; Where e+0x or e-0x is scientific notation, and e+01 represents... e-01 indicates .

11. The method according to any one of claims 6-10, characterized in that, The first signal includes sub-signals within N periods, where N is the length of the first sequence; The first sequence and the GCP are used to determine the first signal, including: The nth element of the first sequence is used to determine a sequence in the GCP, wherein the sequence in the GCP is used to generate a sub-signal within the nth period of the first signal, wherein... .

12. The method according to claim 11, characterized in that, The GCP sequence includes x sequence sum y The sequence, the first signal, the first sequence, and the GCP satisfy the following formula: in, The first signal, It is the nth element of the first sequence. or For the sub-signal within the nth period of the first signal, the x Sequences are used to generate The y Sequences are used to generate , T The period of the sub-signal of the first signal is denoted as .

13. The method according to any one of claims 6-10, characterized in that, The first signal comprises N periodic sub-signals, and the second signal comprises N periodic sub-signals, where N is the length of the first sequence and the second sequence.

14. The method according to claim 13, characterized in that, When the anti-Doppler frequency shift interval is When the second signal is in its nth period, the sub-signal is the product of the conjugate of the nth element of the second sequence and the sub-signal of the first signal in its nth period. .

15. The method according to claim 14, characterized in that, The GCP sequence includes x sequence sum y The sequence, the second signal, the first sequence, the second sequence, and the GCP satisfy the following formula: in, The second signal, The nth element of the second sequence conjugate, It is the nth element of the first sequence. or For the sub-signal within the nth period of the first signal, the x Sequences are used to generate The y Sequences are used to generate , T The period of the sub-signal of the first signal is denoted as .

16. The method according to claim 13, characterized in that, When the anti-Doppler frequency shift interval is When the second signal is in its nth period, the sub-signal is the product of the nth element of the second sequence and the sub-signal of the first signal in its nth period. .

17. The method according to claim 16, characterized in that, The GCP sequence includes x sequence sum y The sequence, the second signal, the first sequence, the second sequence, and the GCP satisfy the following formula: in, The second signal, It is the nth element of the second sequence. It is the nth element of the first sequence. or For the sub-signal within the nth period of the first signal, the x Sequences are used to generate The y Sequences are used to generate , T The period of the sub-signal of the first signal is denoted as .

18. The method according to claim 1 or 2, characterized in that, The method further includes: Send the first signal; Receive the echo signal of the first signal; Perform aperiodic cross-correlation calculation based on the echo signal and the second signal; The distance to the target object is determined based on the result of the aperiodic cross-correlation operation.

19. The method according to claim 1 or 2, characterized in that, The first signal is a single-carrier signal or a multi-carrier signal.

20. A communication device, characterized in that, The communication device includes a module for performing the method as described in any one of claims 1 to 19.

21. A communication device, characterized in that, The communication device includes: a processor; The processor is configured to execute computer programs or instructions to implement the method as described in any one of claims 1 to 19.

22. A computer-readable storage medium, characterized in that, The computer-readable storage medium stores a computer program or instructions that, when executed by a communication device, implement the method as described in any one of claims 1 to 19.

23. A computer program product, characterized in that, When the computer program product is run on a communication device, the method as described in any one of claims 1 to 19 is performed.

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