A control method of a double-switch high-gain converter with coupled inductors

Abstract

The application discloses a double-switch high-gain converter with coupled inductance and a control method, and belongs to the technical field of power electronics. The converter comprises a double-switch input end, a coupled inductance boost unit and an output end. The double-switch input end comprises a power supply V in , a first independent inductor L1, a second independent inductor L2, a first switch S1 and a second switch S2. The double-switch input end is connected with the coupled inductance boost unit. The coupled inductance boost unit comprises a diode D1, a diode D2, a capacitor C1, a capacitor C2, a capacitor C3, a coupled inductance primary winding n p and a coupled inductance secondary winding n s . The output end of the coupled inductance boost unit is connected with the anode of a diode D3. The diode D3 and a capacitor C4 constitute an output part of the converter. The application has the advantages of simple topological structure, super-high output voltage gain, super-low switch voltage stress, convenient switch control and high working efficiency.

Description

Technical Field

[0001] This invention relates to the field of power electronics technology, and more specifically, to a dual-switch high-gain converter with coupled inductors and a control method thereof. Background Technology

[0002] With the drastic depletion of traditional energy reserves, humanity has turned its attention to new energy sources such as solar and wind power. However, solar energy is intermittent due to the day-night cycle, and wind power is periodic with the changing seasons. This results in poor power quality that fails to meet user needs. To address this issue, energy storage devices such as batteries and supercapacitors have been introduced into new energy power generation systems. The DC / DC converter acts as a "bridge" connecting the energy storage devices to the DC bus, and is a key device for enabling energy flow between the two. Furthermore, a DC / DC converter with high gain characteristics is required between the new energy source and the DC bus voltage.

[0003] Based on current research, high-gain DC / DC converters can generally be categorized into isolated and non-isolated types, depending on whether an isolation transformer is incorporated. Isolated DC-DC converters can be further classified into forward, flyback, push-pull, half-bridge, and full-bridge structures. Compared to non-isolated converters, isolated converters have their own transformer, allowing for high gain through adjusting the turns ratio. However, in high-power applications, an excessively large transformer turns ratio can lead to design difficulties, high leakage inductance, and an inability to reduce diode voltage stress, resulting in increased losses and impacting converter performance. Therefore, non-isolated high-gain converters hold significant research value.

[0004] Existing non-isolated high-gain DC-DC converters can be broadly categorized based on their underlying principles: cascaded boost converters based on two-port networks, three-level high-gain converters, high-gain converters with switched capacitors, interleaved parallel high-gain converters, and coupled inductor high-gain converters. With the same input voltage, cascaded circuits produce higher output voltages. However, the voltage stress on the switching devices in subsequent stages of a cascaded converter is higher than that of the preceding stages, and this stress increases with the number of series circuits. Furthermore, a greater number of switching elements are required, leading to higher circuit costs and reduced reliability. Besides cascading, energy storage capacitors are often used to achieve high gain, primarily through the addition of switched capacitors and switched inductors. However, to increase power ratings, large-capacity electrolytic capacitors are typically required, increasing circuit size. Additionally, as the rated current increases, switching losses and EMI problems become more severe. However, there are two problems in the circuits that use coupled inductor technology converters: First, the leakage inductance of the coupled inductor will bring losses, parasitic oscillations and electromagnetic interference, resulting in low circuit efficiency; Second, the diode voltage stress in the circuit is high, which makes the diode performance requirements higher and increases the design cost. Summary of the Invention

[0005] 1. The technical problem that the invention aims to solve To address a series of issues such as power imbalance, complex control, and circuit losses caused by leakage inductance of coupled inductors, this invention provides a dual-switch high-gain converter with coupled inductors and a control method to improve output voltage gain, reduce voltage stress on switching transistors, decrease input current ripple, and expand the input voltage range. This invention employs coupled inductor voltage multiplication technology to achieve higher voltage gain and constructs a leakage inductance energy recovery unit to provide a channel for recycling and reusing the leakage inductance of the coupled inductor. This improves operating efficiency, simplifies control, and enhances operational reliability.

[0006] 2. Technical Solution To achieve the above objectives, the technical solution provided by the present invention is as follows: This invention discloses a dual-switch high-gain converter with coupled inductors, the power supply of which... V in The positive terminal of the transistor is connected to the drain of the second independent inductor L2 and the first switching transistor S1, respectively. The source of the first switching transistor S1 is connected to one end of the first independent inductor L1, and the other end of the first independent inductor L1 is connected to the power supply. V in The negative terminal of the first diode is connected to the first diode, and the other end of the second independent inductor L2 is connected to the drain of the second switching transistor S2, the anode of the diode D1, and one end of the capacitor C1. The source of the second switching transistor S2 is connected to the power supply. V inThe negative terminal of diode D1 is connected to the other end of the first independent inductor L1. The cathode of diode D1 is connected to one end of capacitor C3, and the anode of diode D2 is connected to the primary winding n of the coupling inductor. p The cathode of diode D2 is connected to one end of capacitor C2 and the anode of diode D3. The other end of capacitor C2 is connected to the secondary winding n of the coupling inductor. s The non-identical terminals are connected, and the secondary winding n of the coupled inductor is... s The same terminal is connected to the other end of capacitor C1 and the primary winding n of the coupled inductor. p The non-identical terminals of diode D3 are connected, and the cathode of diode D3 is connected to one end of capacitor C4 and the load R. o One end is connected, and the load R o The other end is connected to the other end of capacitor C4, the other end of capacitor C3, the source of the first switching transistor S1, and one end of the first independent inductor L1.

[0007] This invention discloses a control method for a dual-switch high-gain converter with coupled inductors. In a continuous inductor current mode, the high-gain DC-DC converter employs a control mode where the control signals of the two switches are synchronized, and the two switches are simultaneously turned on and off. This includes six operating modes, which are executed sequentially. The first operating mode: the first switch S1 and the second switch S2 are turned on simultaneously, the diode D3 is turned on, and the diodes D1 and D2 are turned off; The second operating mode: the first switch S1 and the second switch S2 continue to be turned on simultaneously, diode D2 is turned on, and diodes D1 and D3 are turned off; The third working mode: control the first switch S1 and the second switch S2 to continue to be turned on simultaneously, diode D2 is turned on, and diodes D1 and D3 are turned off. The fourth working mode: the first switch S1 and the second switch S2 are turned off simultaneously, diodes D1 and D2 are both turned on, and diode D3 is turned off. The fifth working mode: the first switch S1 and the second switch S2 are kept off, diodes D1 and D3 are both turned on, and diode D2 is turned off. The sixth working mode has the same switching state as the fifth working mode.

[0008] 3. Beneficial effects Compared with existing known technologies, the technical solution provided by this invention has the following significant advantages: (1) A dual-switch high-gain converter with coupled inductor according to the present invention has high output voltage gain characteristics. As shown in formula (6) and Figure 10 As shown, the converter has two degrees of freedom (duty cycle).D and turns ratio n Compared to traditional boost converters, this invention introduces a coupling inductor. By adjusting the duty cycle and the turns ratio of the coupling inductor, the desired voltage gain can be obtained through their combined action. The voltage gain is further improved, and the flexibility is further enhanced. When the duty cycle is 0.6 and the turns ratio is 2, the voltage gain of the converter is as high as 19. The voltage gain can be further extended by simply adjusting the turns ratio.

[0009] (2) A dual-switch high-gain converter with coupled inductor according to the present invention, as shown in formula (7) and Figure 11 As shown, when the duty cycle D Take 0.6, the turns ratio of the coupling inductor n Take 2, coupling coefficient k When the voltage is set to 1, the voltage stress on the switch and diode is only 0.13 and 0.26 times that of the output voltage, respectively, which greatly reduces the voltage stress on the device. The lower voltage stress allows the use of switches and diodes with low on-resistance and low rated voltage, which also minimizes the converter's losses and net cost.

[0010] (3) In this invention, a resonant cavity is constructed at the input terminal, and the switching transistor and diode operate under soft-switching conditions, such as... Figure 13 (b) and (c) Figure 14 As shown in (b), the switching transistor turns on under ZVS conditions, and the power diode achieves smooth turn-on and ZCS turn-off, solving the reverse recovery problem of the diode. All switches and diodes can naturally achieve soft switching. The leakage inductance recovery unit can also recover the energy stored in the coupled inductor, improving gain and power density.

[0011] (4) The dual-switch high-gain converter with coupled inductor of the present invention is versatile and can be applied to various occasions that require high voltage gain, such as energy storage systems, fuel cell power generation systems and switching power supplies. Attached Figure Description

[0012] Figure 1 This is a circuit diagram of a dual-switch high-gain converter with coupled inductor according to the present invention; Figure 2 This is an equivalent circuit diagram of a dual-switch high-gain converter with coupled inductor according to the present invention; Figure 3 This is a schematic diagram of the main operating waveforms of the converter of the present invention in CCM mode; Figure 4 This is a schematic diagram of the equivalent circuit of the converter of the present invention in the first operating mode of CCM mode; Figure 5 This is a schematic diagram of the equivalent circuit of the converter of the present invention in the second operating mode under CCM mode; Figure 6 This is a schematic diagram of the equivalent circuit of the converter of the present invention in the third operating mode under CCM mode; Figure 7 This is a schematic diagram of the equivalent circuit of the converter of the present invention in the fourth operating mode under CCM mode; Figure 8 This is a schematic diagram of the equivalent circuit of the converter of the present invention in the fifth operating mode of CCM mode; Figure 9 This is a schematic diagram of the equivalent circuit of the converter of the present invention in the sixth operating mode of CCM mode; Figure 10 For the converter of the present invention, when the coupling coefficient k=1, the converter voltage gain M With duty cycle D and turns ratio n A graph showing the changes; Figure 11 The converter of this invention has a coupling coefficient k When =1, the voltage stress of the power device is related to the turns ratio of the coupling inductor. n Relationship diagram; Figure 12 (a) in the figure represents the simulated waveforms of the input current and independent inductor current of the converter of the present invention; Figure 12 (b) in the figure is a schematic diagram of the experimental waveform of the independent inductor current; Figure 13 (a) in the figure shows the simulated voltage waveforms of diodes D1, D2, and D3 in the converter of the present invention; Figure 13 (b) in the figure is a schematic diagram of the voltage and current experimental waveforms of the switch S1 and the diode D1; Figure 13 (c) in the figure is a schematic diagram of the experimental waveforms of voltage and current of diodes D2 and D3; Figure 14 (a) shows the simulated voltage and current waveforms of the switching transistors S1 and S2 in the converter of this invention; Figure 14 (b) in the figure is a schematic diagram of the experimental voltage and current waveforms of switching transistors S1 and S2; Figure 15 (a) in the figure represents the simulated waveforms of the input and output voltages of the converter of the present invention; Figure 15 (b) in the figure represents the experimental waveforms of the input and output voltages of the converter; Figure 15 (c) in the figure is a schematic diagram of the transient and steady-state response waveforms of the converter in the open-loop state. Detailed Implementation

[0013] Embodiments of the present invention are described in detail below, examples of which are illustrated in the accompanying drawings, wherein the same or similar reference numerals denote the same or similar elements or elements having the same or similar functions throughout. The embodiments described below with reference to the accompanying drawings are exemplary and intended to explain the present invention, and should not be construed as limiting the present invention.

[0014] Example 1 Combination Figure 1 This embodiment of a dual-switch high-gain converter with coupled inductor includes: a dual-switch input terminal, a coupled inductor boost unit, and an output terminal. The dual-switch input terminal includes a power supply. V in The system consists of a first independent inductor L1, a second independent inductor L2, a first switching transistor S1, and a second switching transistor S2. The input terminals of the two switching transistors are connected to a coupled inductor boost unit, which includes a capacitor C1, a diode D1, a diode D2, a capacitor C2, a capacitor C3, and a primary winding n of the coupled inductor. p and the secondary winding of the coupled inductor n s Among them, capacitor C1, diode D1, and primary winding n of the coupling inductor p A leakage inductance recovery unit is formed, which provides a channel for recycling and reusing the leakage inductance of the coupled inductor; the output terminal of the coupled inductor boost unit is connected to the anode of diode D3, and the two ends of the output terminal are respectively connected to the cathode of diode D3 and one end of capacitor C3. Diode D3 and capacitor C4 constitute the output part of the converter.

[0015] In the dual-switch transistor input terminal, the power supply V in The positive terminal of the first independent inductor S1 is connected to one end of the second independent inductor L2 and the drain of the first switching transistor S1, respectively. The source of the first switching transistor S1 is connected to one end of the first independent inductor L1, and the other end of the first independent inductor L1 is connected to the power supply. V in The negative terminal of the first diode is connected to the first diode, and the other end of the second independent inductor L2 is connected to the drain of the second switching transistor S2, the anode of the diode D1, and one end of the capacitor C1. The source of the second switching transistor S2 is connected to the power supply. V in The negative terminal is connected to the other end of the first independent inductor L1.

[0016] In the coupled inductor boost unit, the cathode of diode D1 and the anode of diode D2, one end of capacitor C3, and the primary winding n of the coupled inductor are connected. p The cathode of diode D2 is connected to one end of capacitor C2, and the other end of capacitor C2 is connected to the secondary winding n of the coupling inductor. s The non-identical terminals are connected, and the secondary winding n of the coupled inductor is... s The same terminal is connected to the other end of capacitor C1 and the primary winding n of the coupled inductor.p The non-same-name ends are connected.

[0017] In the output terminal, the cathode of diode D3 is connected to one end of capacitor C4, and the load R... o One end of capacitor C4 is connected to the load R, and the other end of capacitor C4 is connected to the load R. o The other end is connected.

[0018] The dual-switch high-gain converter with coupled inductor in this embodiment adopts a control mode of simultaneous control signal synchronization of the two switches under CCM, that is, the two switches are turned on and off at the same time. Within one switching cycle, it includes working mode 1, working mode 2, working mode 3, working mode 4, working mode 5, and working mode 6. Figure 3 for Figure 2 The theoretical operating waveform diagram of the equivalent circuit of the converter shown is as follows. Figures 4-9 yes Figure 2 The diagram shows the various operating modes of the equivalent circuit of the converter, and defines the coupling coefficient of the coupled inductor. ,and Among them, the first to sixth working modes correspond to working modes 1-6, specifically as follows: Working mode 1 [t0-t1] Figure 4 ) At time t0, switching transistors S1 and S2 are simultaneously turned on, diode D3 is turned on, and D1 and D2 are turned off. Power supply V in Charging inductors L1 and L2 generates leakage inductance L in the coupled inductors. k Resonance occurs with capacitors C1 and C3, and the power supply V in With clamping capacitor C1 in the magnetizing inductor L m While providing energy, it also charges capacitors C2 and C3. The current flowing through the leakage inductance and the magnetizing inductance decreases rapidly until they are equal, and the secondary winding n... s The current value drops rapidly to zero and then increases in the reverse direction; diode D3 achieves zero-current turn-off (ZCS), and the relevant electrical parameter formulas are as follows: (1) Working mode 2 [t1-t2] Figure 5 ): At time t1, switching transistors S1 and S2 remain on, diode D2 is conducting, and diodes D1 and D3 are off. Power supply V in Continue charging inductors L1 and L2 by inputting current i through inductors L1 and L2. L1 i L2 Gradually increasing. The leakage inductance L of the coupled inductor. k Resonance occurs in the circuit formed by the switching transistors S1 and S2 and the capacitor C3. The clamping capacitor C3 also serves as the magnetizing inductance L. mCapacitor C1 provides energy, using the transformer effect of the coupled inductor to charge the voltage multiplier capacitor C2. At this time, output capacitor C4 charges the load R. o The formulas for the relevant electrical parameters for energy transfer are as follows: (2) Working mode 3 [t2-t3] Figure 6 ): At time t2, switches S1 and S2 remain on, and the power supply... V in Inductors L1 and L2 are charged, and the secondary winding n s The current value drops rapidly to zero, diode D2 conducts, but no current flows. Output capacitor C4 provides energy to the load; the relevant electrical parameter formulas are: (3) Working mode 4 [t3-t4] Figure 7 ): At time t3, switching transistors S1 and S2 are simultaneously turned off, diodes D1 and D2 are turned on, and D3 is turned off. Power supply V in The energy stored in inductors L1 and L2 is released simultaneously to charge C1, C3, and the magnetizing inductor. No current flows through the secondary side of the coupling inductor and diode D2. At time t4, diode D2 is turned off with zero current. The relevant electrical parameter formulas are: (4) Working mode 5 [t4-t5] Figure 8 ): At time t4, switching transistors S1 and S2 remain off, diodes D1 and D3 are on, and D2 is zero-current turn-off (ZCS). V in The energy stored in inductors L1 and L2, along with the energy stored in clamping capacitors C1 and C2, is released simultaneously to charge capacitor C3 and output capacitor C4, while also providing energy to the load. The relevant electrical parameter formulas are as follows: (5) Working mode 6 [t5-t6] Figure 9 ): At time t5, switches S1 and S2 are in the off state. The diode switching is the same as in operating mode 5. Diode D1 remains on, and the current drops rapidly to zero. Zero current turn-off (ZCS) is achieved at time t6. Other operating modes are the same as in mode 5.

[0019] In this embodiment, the dual-switch high-gain converter with coupled inductor, in continuous inductor current mode, with both the first switch S1 and the second switch S2 simultaneously turned on and their duty cycles greater than 0.5, exhibits the following voltage gain: (6) In this embodiment, with coupling coefficient k=1, the converter voltage gain varies with duty cycle. D and turns ratio n The changing curve is as follows Figure 10 As shown, the voltage stress of the converter's switching transistor is also: (7) The converter in this embodiment has a coupling coefficient k When =1, the voltage stress of the converter power devices is related to the turns ratio of the coupling inductor. n The relationship between them is as follows Figure 11 As shown.

[0020] Furthermore, considering the practical situation, since there is leakage inductance in the coupled inductor, the turns ratio of the coupled inductor in the converter of this embodiment is... n 2. Coupling coefficient k When the duty cycle is 0.95 and the duty cycle of the first switch S1 and the second switch S2 is 0.6, the gain of the converter is 18.5 times; if the power supply... V in If the voltage is 12V, then the output voltage of the converter is 222V, and the voltage stress of the switching transistor is only 30V.

[0021] As can be seen, the converter in this embodiment has the advantages of simple topology, ultra-high output voltage gain, ultra-low switching voltage stress, convenient switching control, and high operating efficiency. Based on these advantages, the converter is suitable for applications with wide input voltage range, low voltage input, and high voltage gain.

[0022] To verify the theoretical analysis of the dual-switch high-gain converter with coupled inductor in this embodiment, a simulation platform was built based on the converter simulation parameters in Table 1 below.

[0023]

[0024] Table 1. Converter Simulation Parameters The simulated waveforms of the input current and independent inductor current of the converter in this embodiment under the simulation parameters in Table 1 are as follows: Figure 12 As shown, the simulated waveforms of the voltages of diodes D1, D2, and D3 are as follows: Figure 13 As shown, the change process is basically consistent with the theoretical analysis, and it can be seen that the input current ripple is small and the diode voltage stress is very low.

[0025] Simulated waveforms of switching transistor voltage and current are as follows: Figure 14 As shown, from Figure 14 It can be observed that the voltage stress of the first and second switching transistors S1 and S2 is 30V, which is consistent with the calculation result of the theoretically derived voltage stress expression. Furthermore, it can be seen from the current of the switching transistors that the first and second switching transistors S1 and S2 can achieve zero-current turn-on.

[0026] Input and output voltage simulation waveforms are as follows Figure 15 As shown, it can be observed that when the input voltage is 12V, the output voltage is as high as 220V, which is consistent with the calculation result of the voltage gain expression derived theoretically.

[0027] The simulation results of the simulation platform built based on the parameters listed in Table 1 verified the correctness of the theoretical analysis results, and further strongly demonstrated the advantages of the dual-switch high-gain converter with coupled inductor, namely ultra-high voltage gain and ultra-low device voltage stress. Therefore, in this embodiment, the converter and control method proposed based on the dual-switch input terminal, coupled inductor boost unit, and output terminal circuit have ultra-high voltage gain, with a voltage gain of [missing value]. and ultra-low device voltage stress, device voltage stress is ,in n The turns ratio of the coupled inductor. D Let S1 be the duty cycle of the first switch S1 and the second switch S2.

[0028] It is worth noting that the terms "first" and "second" are used for descriptive purposes only and should not be construed as indicating or implying relative importance or implicitly specifying the number of technical features indicated. Therefore, a feature defined as "first" or "second" may explicitly or implicitly include at least one of that feature. In the description of this invention, "a plurality of" means at least two, such as two, three, etc., unless otherwise explicitly specified.

Claims

1. A control method for a dual-switch high-gain converter with coupled inductors, characterized in that: The converter includes a dual-switch input terminal, a coupled inductor boost unit, and an output terminal; the dual-switch input terminal includes a power supply V. in The system consists of a first independent inductor L1, a second independent inductor L2, a first switching transistor S1, and a second switching transistor S2. The input terminals of the two switching transistors are connected to a coupled inductor boost unit, which includes a capacitor C1, a diode D1, a diode D2, a capacitor C2, a capacitor C3, and a primary winding n of the coupled inductor. p and the secondary winding of the coupled inductor n s Among them, capacitor C1, diode D1, and primary winding n of the coupling inductor p The leakage inductance recovery unit is formed; the output terminal of the coupled inductor boost unit is connected to the anode of diode D3, and the two ends of the output terminal are respectively connected to the cathode of diode D3 and one end of capacitor C3. Diode D3 and capacitor C4 constitute the output part of the converter. In the dual-switch transistor input terminal, the power supply V in The positive terminal of the first independent inductor S1 is connected to one end of the second independent inductor L2 and the drain of the first switching transistor S1, respectively. The source of the first switching transistor S1 is connected to one end of the first independent inductor L1, and the other end of the first independent inductor L1 is connected to the power supply. V in The negative terminal of the first diode is connected to the first diode, and the other end of the second independent inductor L2 is connected to the drain of the second switching transistor S2, the anode of the diode D1, and one end of the capacitor C1. The source of the second switching transistor S2 is connected to the power supply. V in The negative terminal is connected to the other end of the first independent inductor L1; In the coupled inductor boost unit, the cathode of diode D1 and the anode of diode D2, the other end of capacitor C3, and the primary winding n of the coupled inductor are connected. p The cathode of diode D2 is connected to one end of capacitor C2, and the other end of capacitor C2 is connected to the secondary winding n of the coupling inductor. s The non-identical terminals are connected, and the secondary winding n of the coupled inductor is... s The same terminal is connected to the other end of capacitor C1 and the primary winding n of the coupled inductor. p Connect the non-same-named ends; In the output terminal, the cathode of diode D3 is connected to one end of capacitor C4 and the load. R o One end of capacitor C4 is connected to the load, and the other end of capacitor C4 is connected to the load. R o The other end is connected; In continuous inductor current mode, a control method is adopted that synchronizes the control signals of two switching transistors, allowing both transistors to be turned on and off simultaneously. This includes six operating modes, which are executed sequentially. The first operating mode: the first switch S1 and the second switch S2 are turned on simultaneously, the diode D3 is turned on, and the diodes D1 and D2 are turned off; The second operating mode: The first switch S1 and the second switch S2 continue to be simultaneously turned on, diode D2 is turned on, and diodes D1 and D3 are turned off; power supply... V in The first independent inductor L1 and the second independent inductor L2 are charged, and the current i flowing through the first independent inductor L1 and the second independent inductor L2 is... L1 i L2 Gradually increasing; leakage inductance L of the coupled inductor k Resonance occurs in the circuit formed by the first switch S1, the second switch S2, and the capacitor C3. The capacitor C3 also serves as the magnetizing inductor L. m Capacitor C1 provides energy, and the transformer effect of the coupled inductor is used to charge capacitor C2; The third operating mode: Controlling the first switch S1 and the second switch S2 to continue conducting simultaneously, power supply... V in The first independent inductor L1 and the second independent inductor L2 are charged, and the secondary winding n of the coupled inductor is charged. s The current value drops rapidly to zero, diode D2 conducts, but no current flows through it, while diodes D1 and D3 are turned off; The fourth working mode: the first switch S1 and the second switch S2 are turned off simultaneously, diodes D1 and D2 are both turned on, and diode D3 is turned off. The fifth working mode: the first switch S1 and the second switch S2 are kept off, diodes D1 and D3 are both turned on, and diode D2 is turned off. The sixth working mode has the same switching state as the fifth working mode.

2. The control method for a dual-switch high-gain converter with coupled inductors according to claim 1, characterized in that: In continuous inductor current mode, when the first switch S1 and the second switch S2 are simultaneously turned on and off, and the duty cycle is greater than 0.5, the voltage gain is: In the formula, n The turns ratio of the coupled inductor. k Let be the coupling coefficient of the coupled inductor. D This refers to the duty cycle.

3. The control method for a dual-switch high-gain converter with coupled inductors according to claim 2, characterized in that: In continuous inductor current mode, the first switch S1 and the second switch S2 are simultaneously turned on and off, and the voltage stress on the switches is: In the formula, n The turns ratio of the coupled inductor. k Let be the coupling coefficient of the coupled inductor. D Duty cycle, Vo This is the output voltage.

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