A low profile filter-embedded resonant antenna based on metal-bridge loading

Abstract

The present application relates to a kind of low profile filter medium resonator antennas based on metal bridge loading, comprising: first dielectric substrate, metal ground plate and second dielectric substrate are sequentially arranged from top to bottom;The upper surface of first dielectric substrate is provided with rectangular center medium resonator;Two sides of center medium resonator are respectively spaced apart one rectangular edge medium resonator;The interval region of center medium resonator and edge medium resonator is provided with metal bridge, and metal bridge is used to generate high-frequency radiation zero point;Rectangular slot is opened in metal ground plate, and rectangular slot is used for slot coupling feed;The lower surface of second dielectric substrate is provided with feed line;The one end of feed line is provided with first short-circuit via, and first short-circuit via is used to generate low-frequency radiation zero point.Two independent adjustable radiation zero points generated on both sides of passband, effectively improve the frequency selectivity and the out-of-band rejection level in stopband, realize miniaturization, can be widely applied to modern wireless communication system.

Description

Technical Field

[0001] This invention belongs to the field of antenna technology, specifically relating to a low-profile filter dielectric resonator antenna based on metal bridge loading. Background Technology

[0002] With the rapid development of modern wireless communication systems, the coexistence of different types of mobile communication systems has become a current trend. However, when systems of different frequency bands are crowded in a confined space, the coupling between antennas operating in adjacent frequency bands can significantly impact the performance of the communication system. This necessitates the use of additional decoupling techniques to mitigate this impact. Filtered antennas themselves can achieve inter-frequency decoupling. When the passband of one antenna is located in the stopband of another, the energy in the stopband can be effectively suppressed, resulting in minimal interference to antennas in that frequency band, and the coupling between them can be significantly reduced. This eliminates the need for additional decoupling structures between antenna arrays, reducing design complexity to some extent.

[0003] The dielectric resonator antenna (DRA) was first proposed by Professor Long in 1983. Compared to other antennas, DRAs have many advantages. First, because the radiator has no metal parts, it does not experience surface wave loss or conductor loss, thus exhibiting high radiation efficiency even in the millimeter-wave band. Second, DRAs have a rich resonant mode range, allowing for flexible design based on specific needs. Furthermore, since the shape, size, and dielectric constant of the dielectric resonator determine the DRA's operating frequency and radiation characteristics, various three-dimensional shapes can be designed according to actual requirements, and different materials can be selected, offering a high degree of design freedom. Therefore, using DRAs for filtering antenna design can achieve good filtering characteristics while maintaining the advantages of DRAs. However, existing filtering dielectric resonator antennas have relatively high profiles, making it difficult to meet the miniaturization requirements of modern communication systems. Summary of the Invention

[0004] To address the aforementioned problems in the prior art, this invention provides a low-profile filtered dielectric resonator antenna based on metal bridge loading. The technical problem to be solved by this invention is achieved through the following technical solution:

[0005] This invention provides a low-profile filtered dielectric resonator antenna based on metal bridge loading, comprising: a first dielectric substrate, a metal ground plane, and a second dielectric substrate arranged sequentially from top to bottom;

[0006] A rectangular central dielectric resonator is disposed on the upper surface of the first dielectric substrate;

[0007] A rectangular edge dielectric resonator is provided at intervals on both sides of the central dielectric resonator.

[0008] Metal bridges are provided in the interval regions of the central dielectric resonator and the edge dielectric resonator, and the metal bridges are used to generate high-frequency radiation zero points.

[0009] A rectangular slot is provided on the metal ground plane, and the rectangular slot is used for slot coupling power supply.

[0010] The lower surface of the second dielectric substrate is provided with a feed line;

[0011] One end of the feeder is provided with a first short-circuit via, which is used to generate a low-frequency radiation null point.

[0012] In one specific embodiment, the feed line includes a first microstrip line and a second microstrip line;

[0013] The major axes of the first microstrip line and the second microstrip line are located on the same axis.

[0014] The length of the first microstrip line is greater than the length of the second microstrip line;

[0015] The width of the first microstrip line is smaller than the width of the second microstrip line;

[0016] The first microstrip line has a first short-circuit via at one end and a first connection point at the other end;

[0017] The first connection point is used to connect one end of the second microstrip line;

[0018] The other end of the second microstrip line is located at the middle of one edge of the lower surface of the second dielectric substrate and extends toward the center of the second dielectric substrate.

[0019] In one specific embodiment, a second connection point is provided on the first microstrip line near the second microstrip line, and the second connection point is used to connect a lateral branch perpendicular to the feed line;

[0020] The two ends of the horizontal branch are respectively provided with cross-shaped branches;

[0021] The cruciform branch includes a first branch and a second branch;

[0022] The first branch is perpendicular to the second branch and the transverse branch, with one end connected to the transverse branch and the other end provided with a second short-circuit through hole;

[0023] The second branch is parallel to the transverse branch.

[0024] In one specific embodiment, the lower surface of the second dielectric substrate is further provided with L-shaped branches;

[0025] The L-shaped branch is disposed between the first connection point and the second connection point, and is located on both sides of the first microstrip line;

[0026] The short side of the L-shaped branch is parallel to the first microstrip line;

[0027] The long side of the L-shaped branch is parallel to the transverse branch;

[0028] The long side of the L-shaped branch is provided with a second short-path hole.

[0029] In one specific embodiment, the metal bridge is provided with metal pillars.

[0030] In one specific embodiment, the major axis of the central dielectric resonator, the major axis of the edge dielectric resonator, the major axis of the feed line, and the major axis of the metal bridge are parallel.

[0031] In one specific embodiment, the central dielectric resonator is disposed at the center of the upper surface of the first dielectric substrate;

[0032] The two edge dielectric resonators are symmetrically arranged about the center dielectric resonator.

[0033] In one specific embodiment, the length of the first dielectric substrate, the length of the metal ground plane, and the length of the second dielectric substrate are the same;

[0034] The width of the first dielectric substrate, the width of the metal ground plane, and the width of the second dielectric substrate are the same;

[0035] The center of the first dielectric substrate, the center of the metal ground plane, and the center of the second dielectric substrate are located on the same axis.

[0036] In one specific embodiment, the center of the rectangular slot and the center of the central dielectric resonator are located on the same axis; the rectangular slot is located on the metal ground plane below the central dielectric resonator.

[0037] In one specific embodiment, the long axis of the rectangular slit is perpendicular to the long axis of the feed line.

[0038] Compared with existing technologies, the advantages of this invention are as follows: This invention provides a low-profile filtered dielectric resonator antenna based on metal bridge loading. By setting a first short-circuit via at the end of the feed line, a low-frequency radiation null is generated near the lower edge of the passband. Furthermore, a metal bridge is placed in the region between the three dielectric resonators, generating a high-frequency radiation null near the upper edge of the passband. The two independently adjustable radiation nulls generated on both sides of the passband effectively improve frequency selectivity and out-of-band rejection within the stopband. This filtered dielectric resonator antenna has a minimum profile of only 0.09λ0, achieving miniaturization and enabling its widespread application in modern wireless communication systems. Attached Figure Description

[0039] Figure 1 This is a schematic diagram of a low-profile filter dielectric resonator antenna based on metal bridge loading provided in an embodiment of the present invention;

[0040] Figure 2 This is a schematic diagram of a low-profile filter dielectric resonator antenna based on metal bridge loading provided in an embodiment of the present invention;

[0041] Figure 3 This is a schematic diagram of a low-profile filter dielectric resonator antenna based on metal bridge loading provided in an embodiment of the present invention;

[0042] Figure 4 This is a curve showing the reflection coefficient of a low-profile filter dielectric resonator antenna based on metal bridge loading in the 6-16 GHz range, provided by an embodiment of the present invention.

[0043] Figure 5 This is a gain curve of a low-profile filter dielectric resonator antenna based on metal bridge loading in the 6-16 GHz range provided by an embodiment of the present invention.

[0044] Figures 6a-6f This invention provides an embodiment of a low-profile filter dielectric resonator antenna based on a metal bridge loading, showing the E-plane and H-plane radiation patterns at three resonant points within the 6-16 GHz passband.

[0045] Figure label:

[0046] 1: First dielectric substrate; 2: Second dielectric substrate; 3: Center dielectric resonator; 4: Edge dielectric resonator; 5: Metal pillar; 6: Metal bridge; 7: Metal ground plane; 8: Rectangular slot; 9: First short-circuit via; 10: Feeder; 11: Lateral stub; 12: Second short-circuit via; 13: Cross-shaped stub; 14: L-shaped stub. Detailed Implementation

[0047] The present invention will be further described in detail below with reference to specific embodiments, but the implementation of the present invention is not limited thereto.

[0048] Example 1

[0049] Please see Figure 1 A low-profile filtered dielectric resonator antenna based on metal bridge loading includes: a first dielectric substrate 1, a metal ground plane 7, and a second dielectric substrate 2 arranged sequentially from top to bottom. A rectangular central dielectric resonator 3 is disposed on the upper surface of the first dielectric substrate 1, and a rectangular edge dielectric resonator 4 is disposed on each side of the central dielectric resonator 3 at intervals. Metal bridges 6 are disposed in the intervals between the central dielectric resonator 3 and the edge dielectric resonators 4, and the metal bridges 6 are used to generate high-frequency radiation nulls. A rectangular slot 8 is formed on the metal ground plane 7, and the rectangular slot 8 is used for slot-coupled feeding. A feed line 10 is disposed on the lower surface of the second dielectric substrate 2, and a first short-circuit via 9 is disposed at one end of the feed line 10, and the first short-circuit via 9 is used to generate low-frequency radiation nulls.

[0050] This embodiment presents a low-profile filtered dielectric resonator antenna based on a metal bridge loading. A first short-circuit via 9 is placed at the end of the feed line 10, thereby generating a low-frequency radiation null near the lower edge of the passband. A metal bridge 6 is placed in the region between the three dielectric resonators, thereby generating a high-frequency radiation null near the upper edge of the passband. The two independently adjustable radiation nulls generated on both sides of the passband effectively improve frequency selectivity and out-of-band rejection within the stopband.

[0051] Furthermore, the feed line 10 includes a first microstrip line and a second microstrip line. The major axes of the first and second microstrip lines are located on the same axis, the length of the first microstrip line is greater than the length of the second microstrip line, and the width of the first microstrip line is less than the width of the second microstrip line. One end of the first microstrip line is provided with a first short-circuit via 9, and the other end of the first microstrip line is a first connection point used to connect to one end of the second microstrip line. The other end of the second microstrip line is located at the middle position of one edge of the lower surface of the second dielectric substrate 2 and extends towards the center of the second dielectric substrate 2.

[0052] Specifically, the feed line 10 consists of a first microstrip line and a second microstrip line. The first microstrip line is long and narrow, while the second microstrip line is short and wide. The major axis of the feed line 10 is located on the central axis of the first dielectric substrate 1. The feed line 10 is used to introduce a new resonant mode.

[0053] Preferably, the length of the first microstrip line is 11.7 mm and the width of the first microstrip line is 0.65 mm. The length of the second microstrip line is 4 mm and the width of the second microstrip line is 1.2 mm.

[0054] Furthermore, a second connection point is provided on the first microstrip line near the second microstrip line. This second connection point is used to connect to the lateral stub 11 perpendicular to the feed line 10. Cross-shaped stubs 13 are provided at both ends of the lateral stub 11, each stub including a first stub and a second stub. The first stub is perpendicular to both the second stub and the lateral stub 11, while the second stub is parallel to the lateral stub 11. One end of the first stub is connected to the lateral stub 11, and the other end is provided with a second short-circuit via 12. The first stub is connected to the metal ground plane 7 through the second short-circuit via 12.

[0055] Preferably, the transverse branch 11 includes a main branch and a connecting branch. One end of the main branch is connected to a second connection point, and the other end of the main branch is connected to one end of the connecting branch. The other end of the connecting branch is connected to the first branch of the cross-shaped branch 13. The distance between the first connection point and the center of the substrate is 4.65 mm. The main branch of the transverse branch has a length of 4.7 mm and a width of 0.7 mm. The connecting branch of the transverse branch has a length of 1.6 mm and a width of 0.3 mm. The first branch of the cross-shaped branch 13 has a length of 3.2 mm and a width of 0.3 mm. The second branch of the cross-shaped branch 13 has a length of 1 mm and a width of 0.3 mm.

[0056] In this embodiment, a low-profile filter dielectric resonator antenna based on metal bridge loading is connected to a transverse stub 11 via a feed line 10 and extends from the end of the stub to a pair of bent cross-shaped stubs 13 with end-loaded second short-circuit vias 12. This introduces a new resonant mode, broadens the impedance bandwidth, and improves the out-of-band suppression effect of the high-frequency stopband.

[0057] Furthermore, the lower surface of the second dielectric substrate 2 is also provided with an L-shaped stub 14, which is disposed on both sides of the first microstrip line between the first connection point and the second connection point. The short side of the L-shaped stub 14 is parallel to the first microstrip line, and the long side of the L-shaped stub 14 is parallel to the transverse stub 11. A second short-circuit via 12 is provided at the end of the long side of the L-shaped stub 14. The end of the long side of the L-shaped stub 14 is connected to the ground plane through the cylindrical second short-circuit via 12.

[0058] Preferably, the distance between the short side of the L-shaped branch 14 and the feed line 10 is 0.1 mm, and the distance between the long side of the L-shaped branch 14 and the transverse branch 11 is also 0.1 mm. The long side of the L-shaped branch 14 has a length of 4.9 mm and a width of 0.3 mm. The short side of the L-shaped branch 14 has a length of 0.8 mm and a width of 0.3 mm.

[0059] In this embodiment, a low-profile filtered dielectric resonator antenna based on metal bridge loading is provided. By adding a pair of L-shaped stubs 14 with second short-circuit vias 12 at the ends on both sides of the feed line 10, the electric field inside the dielectric resonator and the current distribution on the feed line 10 are disturbed, thereby further improving the impedance matching effect of the antenna in the passband.

[0060] Furthermore, metal pillars 5 are provided on the metal bridge 6. Preferably, two metal pillars 5 are provided on each metal bridge 6, symmetrical about the center of the metal bridge 6. The metal pillars 5 can disturb the electric field inside the dielectric resonator, further improving the impedance matching effect of the antenna in the passband.

[0061] Furthermore, the major axes of the central dielectric resonator 3, the edge dielectric resonators 4, the feed line 10, and the metal bridge 6 are parallel. The central dielectric resonator 3 is located at the center of the upper surface of the first dielectric substrate 1, and the two edge dielectric resonators 4 are symmetrically arranged about the central dielectric resonator 3. The length of the first dielectric substrate 1, the length of the metal ground plane 7, and the length of the second dielectric substrate 2 are the same. The width of the first dielectric substrate 1, the width of the metal ground plane 7, and the width of the second dielectric substrate 2 are the same. The centers of the first dielectric substrate 1, the center of the metal ground plane 7, and the center of the second dielectric substrate 2 are located on the same axis. The center of the rectangular slot 8 and the center of the central dielectric resonator 3 are located on the same axis, and the rectangular slot 8 is located on the metal ground plane 7 below the central dielectric resonator 3. The major axis of the rectangular slot 8 is perpendicular to the major axis of the feed line 10.

[0062] Specifically, the first dielectric substrate 1 and the second dielectric substrate 2 have the same length and width, and the metal ground plane 7 completely covers the lower surface of the first dielectric substrate 1 and the upper surface of the second dielectric substrate 2. The central dielectric resonator 3, the rectangular slot 8, the center of the first dielectric substrate 1, the center of the metal ground plane 7, and the center of the second dielectric substrate 2 are all located on the same axis.

[0063] Preferably, the center dielectric resonator 3, the edge dielectric resonator 4, and the metal bridge 6 have the same length. The first dielectric substrate 1 is a Rogers plate with a relative permittivity of 3.55 and a diameter of 20mm*20mm*0.8mm (length*width*height). The second dielectric substrate 2 is a Rogers plate with a relative permittivity of 3.55 and a diameter of 20mm*20mm*0.5mm (length*width*height). The metal ground plane 7 is a rectangular structure with a diameter of 20mm*20mm (length*width). The rectangular gap 8 has a length of 5mm and a width of 0.7mm. The center dielectric resonator 3 is made of rectangular dielectric ceramic with a relative permittivity of 44, and has a length of 10mm, a width of 5.2mm, and a height of 0.56mm. The edge dielectric resonator 4 is made of rectangular dielectric ceramic with a relative permittivity of 69, and has a length of 10mm, a width of 1.1mm, and a height of 1.2mm. The metal bridge 6 is a rectangular structure with a length of 10 mm and a width of 1.3 mm. The four metal pillars 5 on the metal bridge 6 are symmetrically distributed about the major axis of the rectangular gap 8 and the major axis of the feed line 10, and the diameter of each metal pillar 5 is 1 mm. The first short-circuit via 9 and the second short-circuit via 12 are both cylindrical structures with a height of 0.5 mm.

[0064] The advantages of this invention can be further illustrated by the following simulations:

[0065] Simulation 1: The reflection coefficient of the filter dielectric resonator antenna provided in this embodiment in the 6GHz-16GHz frequency band was simulated and calculated using the commercial simulation software HFSS_19.0. The results are as follows: Figure 4 As shown.

[0066] from Figure 4 It can be seen that the reflection coefficient amplitude of the filter dielectric resonator antenna is less than -10dB within the 10.1-11.81GHz range, indicating that there is good impedance matching in this frequency band.

[0067] Simulation 2: The gain of the filter dielectric resonator antenna provided in this embodiment as a function of frequency in the 6-16GHz frequency band was simulated using the commercial simulation software HFSS_19.0. The results are as follows: Figure 5 As shown.

[0068] from Figure 5 As can be seen, the average gain of the filter dielectric resonator antenna in the passband is 6.3 dBi, and two radiation nulls are generated at the 8.9 GHz and 12.2 GHz frequencies at the edge of the passband. The out-of-band suppression level in the stopband is better than 15 dB. Simulation results show that, compared with the prior art, the present invention achieves good radiation and filtering performance while having a lower profile in the filter dielectric resonator antenna.

[0069] Simulation 3: The E-plane and H-plane radiation patterns of the filter dielectric resonator antenna provided in this embodiment at three resonant points within the 6-16 GHz passband were simulated using the commercial simulation software HFSS_19.0. The results are as follows: Figures 6a-6f As shown.

[0070] from Figures 6a-6f It can be seen that the E-plane and H-plane radiation patterns of the filter dielectric resonator antenna at the three resonant points in the 6-16 GHz band are 25 dB higher at the main polarization level directly above (θ = 0°) than the cross-polarization level, indicating that it has better radiation characteristics in this frequency band.

[0071] This embodiment provides a low-profile filtered dielectric resonator antenna based on metal bridge loading. A low-frequency radiation null is generated near the lower edge of the passband by setting a first short-circuit via 9 at the end of the feed line 10, and a high-frequency radiation null is generated near the upper edge of the passband by setting a metal bridge 6 in the region between the three dielectric resonators. The two independently adjustable radiation nulls generated on both sides of the passband effectively improve frequency selectivity and out-of-band suppression in the stopband. Connecting a lateral stub 11 to the feed line 10 and extending a pair of cross-shaped stubs 13 with second short-circuit vias 12 at the ends of the stub widens the impedance bandwidth while improving the out-of-band suppression effect in the high-frequency stopband. By setting metal pillars 5 on the metal bridge 6 and adding a pair of L-shaped stubs 14 with second short-circuit vias 12 at the ends on both sides of the feed line 10, the impedance matching effect of the antenna in the passband can be further improved. Compared with existing filter dielectric resonator antennas, the filter dielectric resonator antenna provided in this embodiment has the lowest profile of only 0.09λ0, which achieves miniaturization and can be widely used in modern wireless communication systems.

[0072] The above description, in conjunction with specific preferred embodiments, provides a further detailed explanation of the present invention. It should not be construed that the specific implementation of the present invention is limited to these descriptions. For those skilled in the art, various simple deductions or substitutions can be made without departing from the concept of the present invention, and all such modifications and substitutions should be considered within the scope of protection of the present invention.

Claims

1. A low-profile filtered dielectric resonator antenna based on metal bridge loading, characterized in that, include: The first dielectric substrate (1), the metal ground plane (7), and the second dielectric substrate (2) are arranged sequentially from top to bottom; A rectangular central dielectric resonator (3) is disposed on the upper surface of the first dielectric substrate (1); A rectangular edge dielectric resonator (4) is provided on each side of the central dielectric resonator (3) at intervals. Metal bridges (6) are provided in the interval regions of the central dielectric resonator (3) and the edge dielectric resonator (4), and the metal bridges (6) are used to generate high-frequency radiation zero points. A rectangular slot (8) is provided on the metal ground plate (7), and the rectangular slot (8) is used for slot coupling power supply; The lower surface of the second dielectric substrate (2) is provided with a feed line (10); One end of the feeder (10) is provided with a first short-circuit via (9), which is used to generate a low-frequency radiation null point; The feed line (10) includes a first microstrip line and a second microstrip line; The major axes of the first microstrip line and the second microstrip line are located on the same axis. The length of the first microstrip line is greater than the length of the second microstrip line; The width of the first microstrip line is smaller than the width of the second microstrip line; The first microstrip line has a first short-circuit via (9) at one end and a first connection point at the other end; The first connection point is used to connect one end of the second microstrip line; The other end of the second microstrip line is located at the middle position of one edge of the lower surface of the second dielectric substrate (2) and extends toward the center of the second dielectric substrate (2); A second connection point is provided on the first microstrip line near the second microstrip line. The second connection point is used to connect a transverse branch (11) perpendicular to the feed line (10). The two ends of the transverse branch (11) are respectively provided with cross-shaped branches (13); The cruciform branch (13) includes a first branch and a second branch; The first branch is perpendicular to the second branch and the transverse branch (11), with one end connected to the transverse branch (11) and the other end provided with a second short-circuit through hole (12); The second branch is parallel to the transverse branch (11).

2. The low-profile filter dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, The lower surface of the second dielectric substrate (2) is also provided with an L-shaped branch (14); The L-shaped stub (14) is disposed between the first connection point and the second connection point, and is located on both sides of the first microstrip line; The short side of the L-shaped branch (14) is parallel to the first microstrip line; The long side of the L-shaped branch (14) is parallel to the transverse branch (11); The long side of the L-shaped branch (14) is provided with a second short-circuit hole (12).

3. The low-profile filter dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, Metal pillars (5) are provided on the metal bridge (6).

4. The low-profile filter dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, The major axis of the central dielectric resonator (3), the major axis of the edge dielectric resonator (4), the major axis of the feed line (10), and the major axis of the metal bridge (6) are parallel.

5. A low-profile filtered dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, The central dielectric resonator (3) is disposed at the center of the upper surface of the first dielectric substrate (1); The two edge dielectric resonators (4) are symmetrically arranged about the center dielectric resonator (3).

6. The low-profile filter dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, The lengths of the first dielectric substrate (1), the metal ground plane (7), and the second dielectric substrate (2) are the same; The width of the first dielectric substrate (1), the width of the metal ground plane (7), and the width of the second dielectric substrate (2) are the same; The center of the first dielectric substrate (1), the center of the metal ground plane (7), and the center of the second dielectric substrate (2) are located on the same axis.

7. A low-profile filtered dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, The center of the rectangular slot (8) and the center of the central dielectric resonator (3) are on the same axis; the rectangular slot (8) is located on the metal ground plane (7) below the central dielectric resonator (3).

8. A low-profile filtered dielectric resonator antenna based on metal bridge loading according to claim 1, characterized in that, The long axis of the rectangular slit (8) is perpendicular to the long axis of the feed line (10).

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