Portable neutron personal dosimeter

Abstract

The portable neutron personal dosimeter disclosed by the embodiment of the application comprises a silicon semiconductor detector unit for detecting neutron radiation and generating a corresponding electric signal, a preamplifier circuit unit connected with the silicon semiconductor detector unit, for processing the detected neutron radiation electric signal and converting it into a pulse signal, an information processing unit connected with the preamplifier circuit unit, for processing the pulse signal and outputting neutron dose information, a power supply circuit unit for providing appropriate voltages to the silicon semiconductor detector unit, the preamplifier circuit unit and the information processing unit respectively, a display screen unit connected with the information processing unit, for displaying the neutron dose information, and an alarm unit connected with the information processing unit, for outputting an alarm signal. The portable neutron personal dosimeter device has a simple structure, is easy to use, can accurately detect neutron radiation, can realize good protection of individuals, and has a good application prospect in the field of neutron radiation detection.

Description

Technical Field

[0001] This invention belongs to the field of radiation detection technology, specifically relating to a portable neutron personal dosimeter. Background Technology

[0002] Neutrons are neutral particles that pose a radiation hazard to many materials and biological tissues. Therefore, monitoring and measuring neutron radiation is crucial for radiation protection and safety. A neutron dose rate meter is a device used to measure the dose rate of neutron radiation. Portable personal neutron dosimeters can detect neutron radiation, providing real-time information on individual radiation dose equivalent rate and dose equivalent for nuclear personnel, and providing timely warnings of potential radiation exceedances, protecting them from excessive nuclear radiation harm. However, current portable neutron dosimeters have low accuracy in neutron radiation detection and cannot accurately predict personnel radiation exposure, thus failing to provide adequate personal protection. Summary of the Invention

[0003] In view of this, some embodiments disclose a portable neutron personal dosimeter, including:

[0004] A silicon semiconductor detector unit is used to detect neutron radiation and generate a corresponding electrical signal;

[0005] The preamplifier circuit unit is connected to the silicon semiconductor detector unit to process the detected neutron radiation electrical signal and convert it into a pulse signal;

[0006] The information processing unit is configured to be connected to the preamplifier circuit unit to process pulse signals and output neutron dose information;

[0007] The power supply circuit unit is used to provide appropriate voltages to the silicon semiconductor detector unit, the preamplifier circuit unit, and the information processing unit, respectively.

[0008] The display unit is connected to the information processing unit and is used to display neutron dose information;

[0009] The alarm unit is connected to the information processing unit and is used to output alarm signals.

[0010] Some embodiments of the portable neutron personal dosimeter disclosed include a preamplifier circuit unit comprising:

[0011] The preamplifier module is used to amplify the neutron radiation electrical signal;

[0012] The shaping filter module is used to filter the amplified neutron radiation electrical signal;

[0013] The voltage amplifier module is used to amplify the filtered radiated electrical signal;

[0014] The discrimination comparator module is used to convert the amplified neutron radiation electrical signal into a stable radiation signal.

[0015] Some embodiments of the portable neutron personal dosimeter disclosed include a preamplifier module comprising:

[0016] Operational amplifier U6;

[0017] The fifth and sixth interfaces of the operational amplifier U6 are connected, and further connected to the power supply filter bead FB1. The power supply filter bead FB1 is further connected to the VCC_3V3A power supply.

[0018] The fifth and sixth interface terminals of the operational amplifier U6 are further connected with parallel power supply filter capacitors C24, C25, and C26, which are further grounded.

[0019] The third interface terminal of operational amplifier U6 is connected in sequence to the source of electrostatic discharge protection diode D5, feedback resistor R28, and field-effect transistor Q7; the other end of feedback resistor R28 is connected to VCC_3V3A power supply; electrostatic discharge protection diode D5 is further grounded; the drain of field-effect transistor Q7 is connected to parallel resistor R43 and capacitor C44, and the other end of parallel resistor R43 and capacitor C44 is grounded.

[0020] The fourth interface of operational amplifier U6 is connected to a parallel compensation filter capacitor C39 and a compensation filter resistor R37. The parallel compensation filter capacitor C39 and the compensation filter resistor R37 are further connected to the second interface of operational amplifier U6 and are grounded. The fourth interface of operational amplifier U6 is also connected to a feedback resistor R29. The other end of the feedback resistor R29 is connected to the fifth and sixth interface of operational amplifier U6.

[0021] The gate of the field-effect transistor Q7 is connected to a parallel phase compensation resistor R26 and a phase compensation capacitor C30, which are further connected to the first interface terminal of the operational amplifier U6.

[0022] The gate of the field-effect transistor Q7 is further connected to a DC blocking capacitor C35. C35 is further connected in sequence to a voltage divider and current-limiting resistor R31, a voltage divider and current-limiting resistor R27, and a VCCA_10V power supply. A coaxial interface J2 is connected between C35 and R31, and J2 is grounded. An input filter capacitor C29 is connected between R31 and R27, and C29 is further grounded. An input filter capacitor C27 is connected between R27 and the VCCA_10V power supply, and C27 is further grounded.

[0023] Some embodiments of the portable neutron personal dosimeter disclosed include a shaping filter module comprising:

[0024] Operational amplifier U7A;

[0025] The eighth interface of the operational amplifier U7A is connected to a power supply filter bead FB2, which is further connected to a VCC_3V3A power supply. The eighth interface of the operational amplifier U7A is also connected to parallel power supply filter capacitors C28 and C31, which are further grounded.

[0026] The third interface terminal of operational amplifier U7A is connected in sequence to phase compensation / filter capacitor C38, voltage divider current limiting resistor R34, high-frequency filter capacitor C37, voltage divider current limiting surge resistor R33, filter capacitor C33, and filter resistor R32; phase compensation / filter capacitor C38 is further grounded; resistor R40 and capacitor C36 are connected between voltage divider current limiting resistor R33 and filter capacitor C33, and resistor R40 is further grounded;

[0027] The second interface terminal of the operational amplifier U7A is connected to feedback resistors R44 and R47; feedback resistor R47 is further grounded, feedback resistor R44 is further connected to feedback resistor R45, and feedback resistor R45 is further connected to the first interface terminal of the operational amplifier U7A; high-frequency filter capacitor C37 is further connected between feedback resistor R44 and feedback resistor R45.

[0028] The first interface terminal of the operational amplifier U7A is further connected to capacitor C34, which is further connected to a parallel phase compensation capacitor C42 and a phase compensation resistor R41. The other end of the parallel phase compensation capacitor C42 and the phase compensation resistor R41 is grounded.

[0029] Some embodiments of the portable neutron personal dosimeter disclosed include a voltage amplifier module comprising:

[0030] Operational amplifier U7B;

[0031] The fifth interface terminal of the operational amplifier U7B is configured for connection to the preamplifier circuit.

[0032] The sixth interface of operational amplifier U7B is connected to a parallel feedback resistor R39 and a phase compensation capacitor C43, and is further connected in sequence to an input current limiting / bias resistor R46 and an input filter capacitor C45. The input filter capacitor C45 is further grounded. The parallel feedback resistor R39 and the phase compensation capacitor C43 are further connected to the seventh interface of operational amplifier U7B. The seventh interface of operational amplifier U7B is further connected to an output current limiting resistor R35.

[0033] Some embodiments of the portable neutron personal dosimeter disclose a discrimination comparator module including:

[0034] Operational amplifier U8;

[0035] The third interface of operational amplifier U8 is connected with a parallel filter resistor R38 and a filter capacitor C40; the parallel filter resistor R38 and filter capacitor C40 are further connected to the second interface of operational amplifier U8 and grounded.

[0036] The fourth interface terminal of the operational amplifier U8 is connected to an amplification resistor R42, which is further connected to the second interface terminal of the operational amplifier U8.

[0037] The first interface terminal of the operational amplifier U8 is connected to a filter shaping resistor R36, and the filter shaping resistor R36 is connected to a filter shaping capacitor C41. The filter shaping capacitor C41 is further connected to the second interface terminal of the operational amplifier. The filter shaping resistor R36 and the filter shaping capacitor C41 are connected to the subsequent circuit to transmit the shaped and stable radiated signal to the subsequent circuit.

[0038] The fifth interface of operational amplifier U8 is connected to an amplification resistor R30 and a power supply filter capacitor C32. The power supply filter capacitor C32 is further grounded, and the amplification resistor R30 is further connected to the fourth interface of operational amplifier U8. A VCC_3V3A power supply is connected between the amplification resistor R30 and the power supply filter capacitor C32.

[0039] Some embodiments of the portable neutron personal dosimeter disclose a power supply circuit unit including a buck circuit module, a boost circuit module, a storage circuit module, a switch control circuit module, a button circuit module, and a display interface circuit module.

[0040] Furthermore, some embodiments of the portable neutron personal dosimeter disclose a step-down circuit module including:

[0041] DC-DC converter U1;

[0042] The first and fourth interface terminals of DC-DC converter U1 are connected, and the second interface terminal of DC-DC converter U1 is grounded. An input filter capacitor C1 is connected in parallel between the second interface terminal and the first interface terminal of DC-DC converter U1. The input filter capacitor, the first interface terminal, and the fourth interface terminal are further connected to the input voltage terminal VCC_BAT.

[0043] The third interface of DC-DC converter U1 is connected to inductor L1. Inductor L1 is further connected to one end of feedback and output regulation resistor R4, output filter capacitors C2, C3, and C4 in sequence, and further connected to the output voltage terminal VCC_3V3.

[0044] A feedback and output regulation resistor R7 is connected between the fifth interface terminal and the second interface terminal of the DC-DC converter U1. The fifth interface terminal is further connected to the other end of the feedback and output regulation resistor R4 and the other end of the output filter capacitor C2. The other ends of the output filter capacitors C3 and C4 are grounded.

[0045] The two ends of the output filter capacitor C4 are further connected to the two ends of the protection diode D1 respectively.

[0046] Some embodiments of the portable neutron personal dosimeter disclosed include a boost circuit module comprising:

[0047] Boost converter U3;

[0048] An inductor L2 is connected between the VIN and SW interfaces of the boost converter U3; the EN interface of the boost converter U3 is connected to one end of the resistor R11, and the inductor L2 is connected to the other end of the resistor R11, and further connected to the input voltage terminal VCC_BAT.

[0049] An input filter capacitor C6 is connected between the GND terminal of the boost converter U3 and the input voltage terminal VCC_BAT. The input filter capacitor C6 and the GND terminal of the boost converter U3 are grounded.

[0050] The SW interface of boost converter U3 is further connected to diode D2 and output filter capacitors C9 and C10 in sequence; the FB interface of boost converter U3 is connected to output regulating resistors R12 and R15, with the other end of output regulating resistor R12 connected between diode D2 and output filter capacitor C9, and the other end of output regulating resistor R15 grounded to GND and connected to the other end of output filter capacitors C9 and C10; the output terminal of diode D2 outputs a boosted DC voltage VCC_12V;

[0051] Voltage regulator converter U2;

[0052] The first and third interfaces of the voltage regulator U2 are connected, and further connected to the DC voltage VCC_12V; the second interface of the voltage regulator U2 is grounded; an input filter capacitor C11 is connected in parallel between the second interface and the first interface of the voltage regulator U2.

[0053] The fourth interface of the voltage regulator converter U2 is connected to output adjustment resistors R13, R14, and R16. The fifth interface of the voltage regulator converter U2 is connected sequentially to the other end of output adjustment resistor R13 and one end of output filter capacitors C7 and C8. The other end of output adjustment resistor R16 is connected to the second interface of the voltage regulator converter U2. The other end of output adjustment resistor R14 is connected to the other end of output filter capacitor C7, and the other end of output filter capacitor C8 is connected to the other end of output adjustment resistor R16. The fifth interface of the voltage regulator converter U2 finally outputs a DC voltage VCC_10V after step-down regulation.

[0054] Some embodiments of the portable neutron personal dosimeter disclosed include a storage circuit module comprising:

[0055] Erasable programmable read-only memory U4;

[0056] The first, second, third, and fourth interface terminals of the erasable programmable read-only memory U4 are connected and grounded;

[0057] The eighth interface of the erasable programmable read-only memory U4 is configured to connect to the VCC_3V3 power supply;

[0058] The seventh interface terminal of the erasable programmable read-only memory U4 is grounded;

[0059] The sixth interface terminal of the erasable programmable read-only memory U4 is configured to connect to the I2C_SCL of the system bus;

[0060] The fifth interface terminal of the erasable programmable read-only memory U4 is configured to connect to the system data line I2C_SDA.

[0061] The portable neutron personal dosimeter disclosed in this invention has a simple structure, is easy to use, and can accurately detect neutron radiation, providing good protection for individuals. It has good application prospects in the field of neutron detection. Attached Figure Description

[0062] Figure 1 Schematic diagram of a portable neutron personal dosimeter system;

[0063] Figure 2Schematic diagram of the preamplifier circuit unit;

[0064] Figure 3 Schematic diagram of the preamplifier module;

[0065] Figure 4 A schematic diagram of the shaping filter module;

[0066] Figure 5 A schematic diagram of the amplifier circuit module;

[0067] Figure 6 A schematic diagram of the discriminator comparator module;

[0068] Figure 7 A schematic diagram of the step-down circuit module;

[0069] Figure 8 A schematic diagram of the boost circuit module;

[0070] Figure 9 Schematic diagram of storage circuit module

[0071] Figure 10 Schematic diagram of a portable neutron personal dosimeter

[0072] Figure 11 A schematic diagram of the switch control circuit module;

[0073] Figure 12 Schematic diagram of the button circuit module.

[0074] Figure Labels

[0075] 1. Lower shell 2. Upper shell

[0076] 3 Indicator lights 4 Buzzer

[0077] 5 Display screen 6 First button

[0078] 7 Second button 8 Battery cover Detailed Implementation

[0079] The term "embodiment" used herein, as an example, is not necessarily to be construed as superior to or better than other embodiments. Performance testing in these embodiments of the invention, unless otherwise specified, employs conventional testing methods in the art. It should be understood that the terminology used in these embodiments is merely for describing particular implementations and is not intended to limit the scope of the disclosure of these embodiments.

[0080] Unless otherwise stated, the technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which the embodiments of this invention pertain; other experimental methods and technical means not specifically noted in the embodiments of this invention refer to experimental methods and technical means commonly used by one of ordinary skill in the art.

[0081] The terms “basic” and “approximately” used in this document are to describe small fluctuations. For example, they can mean less than or equal to ±5%, such as less than or equal to ±2%, such as less than or equal to ±1%, such as less than or equal to ±0.5%, such as less than or equal to ±0.2%, such as less than or equal to ±0.1%, such as less than or equal to ±0.05%. Numerical data presented or expressed in range format in this document are used for convenience and brevity only, and should therefore be flexibly interpreted to include not only the explicitly listed values ​​that define the range, but also all independent values ​​or subranges contained within that range. For example, a numerical range of “1–5%” should be interpreted to include not only the explicitly listed values ​​from 1% to 5%, but also the independent values ​​and subranges within the indicated range. Thus, this numerical range includes independent values ​​such as 2%, 3.5%, and 4%, and subranges such as 1%–3%, 2%–4%, and 3%–5%, etc. This principle also applies to ranges that list only one value. Furthermore, this interpretation applies regardless of the width of the range or the characteristics described.

[0082] In this document, including in the claims, conjunctions such as "comprising," "including," "with," "having," "containing," "involving," and "accommodating" are understood to be open-ended, meaning "including but not limited to." Only the conjunctions "consisting of" and "composed of" are closed conjunctions.

[0083] To better illustrate the content of this invention, numerous specific details are provided in the following detailed embodiments. Those skilled in the art should understand that the invention can be practiced even without certain specific details. In the embodiments, some methods, means, instruments, and devices well-known to those skilled in the art are not described in detail, in order to highlight the main points of the invention.

[0084] Without conflict, the technical features disclosed in the embodiments of the present invention can be combined arbitrarily, and the resulting technical solution belongs to the content disclosed in the embodiments of the present invention.

[0085] In some implementations, such as Figure 1 As shown, the portable neutron personal dosimeter includes:

[0086] A silicon semiconductor detector unit is used to detect neutron radiation and generate a corresponding electrical signal;

[0087] The preamplifier circuit unit is connected to the silicon semiconductor detector unit to process the detected neutron radiation electrical signal and convert it into a pulse signal;

[0088] The information processing unit is configured to be connected to the preamplifier circuit unit to process pulse signals and output neutron dose information;

[0089] The power supply circuit unit is used to provide appropriate voltages to the silicon semiconductor detector unit, the preamplifier circuit unit, and the information processing unit, respectively.

[0090] The display unit is connected to the information processing unit and is used to display neutron dose information;

[0091] The alarm unit is connected to the information processing unit and is used to output alarm signals.

[0092] Typically, neutrons enter a silicon semiconductor detector and undergo a nuclear reaction, producing charged particle pairs. These high-energy ionized particles enter the detector's sensitive region, generating electron-hole pairs (the number of which is proportional to the energy of the neutrons deposited in the sensitive region). The movement of electrons and holes under a reverse bias voltage causes changes in the induced charge on the two electrodes, which are ultimately collected in the form of electrical pulses to form the detector's response signal.

[0093] The silicon semiconductor detector unit detects neutrons and outputs electrical signals. These signals are amplified by the preamplifier circuit unit and converted into digital signals. The MCU in the information processing unit then counts these signals. The battery circuit unit supplies power to other functional units. The display unit shows the measurement results. The alarm unit provides alarm information. The buttons provide the operation interface. The LED indicator shows the working status and provides a light alarm. The buzzer provides an audible alarm.

[0094] In some embodiments, such as Figure 2 As shown, the preamplifier circuit unit includes: a preamplifier module for amplifying the neutron radiation signal; a shaping filter module for filtering the amplified neutron radiation signal; a voltage amplifier module for amplifying the filtered radiation signal; and a discrimination comparator module for converting the amplified neutron radiation signal into a stable radiation signal. Typically, the preamplifier circuit unit processes electrical pulse signals to facilitate the radiation particle counting function. It includes a detector interface and pre-acquisition stage, a preamplifier, a filter, a voltage amplifier, a discrimination comparator, and an output and interface stage. It receives weak signals from the detector, amplifies them, filters them, discriminates them, shapes them, and outputs them, ultimately converting them into pulses recognizable by a digital system.

[0095] Some embodiments disclose portable neutron personal dosimeters, such as Figure 3As shown, the preamplifier module includes: operational amplifier U6; the fifth and sixth interfaces of operational amplifier U6 are connected, and further connected to power supply filter bead FB1, which is further connected to VCC_3V3A power supply; the fifth and sixth interfaces of operational amplifier U6 are further connected with parallel power supply filter capacitors C24, C25, and C26, which are connected in parallel. 25. C26 is further grounded; the third interface terminal of operational amplifier U6 is connected in sequence to the source of electrostatic protection diode D5, feedback resistor R28, and field-effect transistor Q7; the other end of feedback resistor R28 is connected to power supply VCC_3V3A; electrostatic protection diode D5 is further grounded; the drain of field-effect transistor Q7 is connected to parallel resistor R43 and capacitor C44, the other end of parallel resistor R43 and capacitor C44 is grounded; the fourth interface terminal of operational amplifier U6 is connected to parallel compensation filter capacitor C39 and compensation filter resistor R37, the parallel compensation filter capacitor C39 and compensation filter resistor R37 are further connected to the second interface terminal of operational amplifier U6 and grounded; the fourth interface terminal of operational amplifier U6 is also connected to feedback resistor R29, the other end of feedback resistor R29 is connected to the fifth and sixth interface terminals of operational amplifier U6; the gate of field-effect transistor Q7 is connected to parallel... A phase compensation resistor R26 and a phase compensation capacitor C30 are connected in parallel. These two resistors are further connected to the first interface terminal of operational amplifier U6, which is then connected to the input terminal of the subsequent circuit. A DC-blocking coupling capacitor C35 is connected to the gate of field-effect transistor Q7. This capacitor is then connected in sequence to voltage divider and current-limiting resistors R31 and R27, and the VCCA_10V power supply. A coaxial interface J2 is connected between the DC-blocking coupling capacitor C35 and the voltage divider and current-limiting resistor R31, and is grounded. An input filter capacitor C29 is connected between the voltage divider and current-limiting resistors R31 and R27, and is further grounded. An input filter capacitor C27 is connected between the voltage divider and current-limiting resistor R27 and the VCCA_10V power supply, and is further grounded.

[0096] Typically, in a preamplifier module circuit:

[0097] The preamplifier module is based on the charge sensitivity amplification circuit of the ADA4807 operational amplifier chip. It adopts a complete conditioning circuit of "filtering → protection → precision amplification → power purification" for the weak high-frequency signal collected by the detector. It uses the ADA4807 operational amplifier to achieve high-precision amplification, providing a clean signal with appropriate amplitude for subsequent processing, and solving the problem of weak signals being easily interfered with and difficult to amplify. The ADA4807 used in operational amplifier U6 is a high-speed, low-noise, high-precision operational amplifier with high bandwidth and low offset voltage, which can effectively amplify weak signals and maintain accuracy.

[0098] The J2 coaxial interface is a COAXIAL coaxial socket, which receives weak external signals. The coaxial structure has strong anti-interference capabilities and is suitable for transmitting high-frequency, low-amplitude signals. The input filter capacitors C27 and C29 (10nF) work together with the voltage divider and current limiting resistors R27 and R31 to filter out high-frequency noise in the input signal and form a simple RC filter to initially purify the signal. The voltage divider and current limiting resistors R27 (100KΩ) and R31 (100MΩ) adjust the amplitude of the input signal, and the high impedance characteristic of R31 can reduce the load impact on weak input signals.

[0099] The DC blocking capacitor C35 (1nF) blocks the DC component in the input signal, allowing only the AC signal to pass through, ensuring that the subsequent amplifier operates at a suitable DC level; the BF862 junction field-effect transistor (JFET) Q7 provides input protection / impedance matching. The high input impedance of the JFET further reduces the load on the preceding signal, while also providing some clamping protection during overvoltage; the ESD protection diode D5 can be a PESD7V3L1UG to achieve ESD protection, preventing electrostatic discharge and surges from damaging the subsequent amplifier through the input port and clamping overvoltage within a safe range.

[0100] Feedback resistors R28 (1KΩ) and R29 (10KΩ) together with operational amplifier U6 form a non-inverting amplifier circuit to amplify the weak input signal to a suitable amplitude. Compensation filter capacitor C39 (0.1μF) and compensation filter resistor R37 (20KΩ) improve the frequency response of operational amplifier U6 (such as phase compensation), avoid self-oscillation, and filter out high-frequency noise after amplification. Phase compensation capacitor C30 (1pF) is connected in parallel in the feedback loop to further optimize the phase margin of the amplifier and ensure the stability of high-frequency signal amplification.

[0101] The VCC_3V3A power supply provides 3.3V to the operational amplifier U6 and its peripheral circuits, and must ensure low noise and high stability. The power supply filter bead FB1 (CBM160808U121T ferrite bead) suppresses high-frequency noise on the power lines, ensuring a clean operating power supply for the op-amp. Power supply filter capacitors C24 (1nF), C25 (0.1μF), and C26 (10μF) provide all-around filtering from high to low frequencies. The 1nF capacitor C24 filters out high-frequency noise, the 0.1μF capacitor C25 filters out intermediate frequency ripple, and the 10μF capacitor C26 stabilizes the power supply voltage to cope with dynamic current changes in the op-amp.

[0102] The TP9 test point is the output signal test point. It can be used to measure the amplitude and frequency of the amplified signal with an oscilloscope, and is used to debug and verify the circuit performance.

[0103] In some embodiments, such as Figure 4 As shown, the shaping filter module includes: an operational amplifier U7A; a power filter bead FB2 is connected to the eighth interface of the operational amplifier U7A, and the power filter bead FB2 is further connected to a VCC_3V3A power supply; the eighth interface of the operational amplifier U7A is also connected to parallel power filter capacitors C28 and C31, and the parallel power filter capacitors C28 and C31 are further grounded to AGND; the third interface of the operational amplifier U7A is sequentially connected to a phase compensation / filter capacitor C38, a voltage divider current limiting resistor R34, a high-frequency filter capacitor C37, a voltage divider current limiting surge resistor R33, a filter capacitor C33, and a filter resistor R32; the phase compensation / filter capacitor C38 is further grounded; a resistor R40 and a capacitor C36 are connected between the voltage divider current limiting resistor R33 and the filter capacitor C33, and the resistor R40 is further grounded; the capacitor C36 is further connected to the output of the preceding circuit. Next, the filter resistor R32 is further connected to the output of the preamplifier circuit, for example, to the first interface terminal of the operational amplifier U6 in the preamplifier module; the second interface terminal of the operational amplifier U7A is connected to feedback resistors R44 and R47; the feedback resistor R47 is further grounded, the feedback resistor R44 is further connected to the feedback resistor R45, and the feedback resistor R45 is further connected to the first interface terminal of the operational amplifier U7A; the high-frequency filter capacitor C37 is further connected between the feedback resistors R44 and R45; the first interface terminal of the operational amplifier U7A is further connected to the capacitor C34, the capacitor C34 is further connected to the parallel phase compensation capacitor C42 and the phase compensation resistor R41, and the other end of the parallel phase compensation capacitor C42 and the phase compensation resistor R41 is grounded to AGND; the pin leading out from the capacitor C34 is the amplified signal output terminal, which can be connected to the subsequent circuit.

[0104] Typically, shaping filter modules are mainly used for filtering, amplifying, and suppressing noise in input signals, primarily for scenarios involving precise processing of weak signals. For a complete conditioning circuit of "filtering → precision amplification → power purification" for weak signals, operational amplifier U7A is used to achieve low-noise, high-precision amplification, providing a clean signal with appropriate amplitude for subsequent processing circuits. Specifically, operational amplifier U7A can be the ADA4505-2. The ADA4505-2 is a low-noise, high-precision, rail-to-rail output operational amplifier with low offset voltage and high common-mode rejection ratio, suitable for weak signal amplification and high-precision signal conditioning, ensuring undistorted and low-noise amplified signals.

[0105] In the shaping filter module, filter resistor R32 (500Ω) and filter capacitor C33 (1nF) form an RC filter network to filter out high-frequency noise in the input signal, initially purifying the signal, and simultaneously providing simple signal attenuation / impedance matching. Voltage divider and current limiting resistors R33 (3KΩ) and R34 (38KΩ) further adjust the input signal amplitude to match the input range of the operational amplifier ADA4505-2, preventing overload; at the same time, the high-precision resistors ensure a stable voltage division ratio without introducing additional errors; the high-frequency filter capacitor C37 (220pF), working in conjunction with the voltage divider and current limiting resistor R34, enhances high-frequency noise filtering, making the signal input to the op-amp cleaner.

[0106] Feedback resistors R47 (100KΩ), R44 (20KΩ), and R45 (336R) together with the operational amplifier ADA4505-2 form an inverting proportional amplifier circuit. Typically, calculations are needed based on the specific values ​​of the feedback resistors to amplify the weak input signal to a suitable amplitude (e.g., from mV to V). A phase compensation / filter capacitor C42 (1nF) is connected in parallel in the feedback loop to optimize the phase margin of the op-amp, prevent high-frequency self-oscillation, and filter out high-frequency noise after amplification, ensuring signal stability.

[0107] The VCC_3V3A power supply provides 3.3V to the operational amplifier U8 and its peripheral circuits, ensuring low noise and high stability. The power supply filter bead FB2 (CBM160808U121T ferrite bead) suppresses high-frequency noise on the power lines, ensuring a clean power supply for the op-amp and preventing noise from coupling into the signal path. The power supply filter capacitors C28 (0.1μF) and C31 (0.1μF) filter out intermediate and high-frequency noise in the power supply, stabilize the power supply voltage, cope with dynamic current changes in the op-amp, and ensure amplification accuracy.

[0108] In some embodiments, such as Figure 5 As shown, the voltage amplifier module includes:

[0109] Operational amplifier U7B;

[0110] The fifth interface terminal of the operational amplifier U7B is configured for connection to the preceding circuitry; for example, it can be connected to the pin leading out of capacitor C34 of the shaping filter module; the fifth interface terminal of the operational amplifier U7B can be configured with a probe point TP7.

[0111] The sixth interface of operational amplifier U7B is connected to a parallel feedback resistor R39 and a phase compensation capacitor C43, and is further connected in sequence to an input current limiting / bias resistor R46 and an input filter capacitor C45. The input filter capacitor C45 is further grounded to AGND. The parallel feedback resistor R39 and phase compensation capacitor C43 are further connected to the seventh interface of operational amplifier U7B. The seventh interface of operational amplifier U7B is further connected to an output current limiting resistor R35. A probe point TP8 can be set at the seventh interface of operational amplifier U7B. The output current limiting resistor R35 is used to connect to subsequent circuits, such as the filter capacitor C40 of the discrimination comparator module.

[0112] Typically, voltage amplifier modules are mainly used for low-noise, high-precision amplification of input signals, and stability is optimized through compensation networks. For the "filtering → precision amplification → stable output" circuit for weak signals, operational amplifier U7B is used to achieve low-noise, high-precision amplification, with stability ensured by a compensation network. This provides a clean signal with appropriate amplitude for subsequent processing, solving the problem of "weak signals being easily overwhelmed by noise and difficult to amplify accurately." Specifically, the operational amplifier U7B can be the ADA4500-2ARZ. The ADA4500-2ARZ is a low-noise, high-precision operational amplifier with wide bandwidth, low offset voltage, and high common-mode rejection ratio (CMRR), used for weak signal amplification and high-precision signal processing, ensuring low distortion and low noise after signal amplification.

[0113] The feedback resistor R39 (10KΩ) and the ADA4500-2ARZ form a non-inverting amplifier circuit, which, through circuit design, can amplify a weak input signal by 11 times. A phase compensation capacitor C43 (10pF) is connected in parallel across the feedback resistor R39 to optimize the op-amp's phase margin, preventing self-oscillation during high-frequency signal amplification and ensuring stable circuit operation. The input current-limiting / bias resistor R46 (1KΩ) provides a DC bias path for the non-inverting input of the operational amplifier U7B, while also limiting the input current and protecting the op-amp's input stage. Combined with the non-inverting amplifier architecture, the input resistor R46 is the input impedance of the amplifier circuit. The input filter capacitor C45 (10μF) and the input current-limiting / bias resistor R46 form an RC filter network to filter out low-frequency noise in the input signal, making the signal input to the op-amp cleaner.

[0114] The output current-limiting resistor R35 (120Ω) limits the op-amp output current, protecting the subsequent load and suppressing high-frequency oscillations at the output. TP7 can be used to detect the input signal at the non-inverting input of the op-amp, and TP8 can be used to detect the amplified output signal, facilitating the measurement of signal amplitude, frequency, noise, etc., using an oscilloscope and multimeter for debugging and verifying circuit performance. AGND is analog ground, providing a low-noise reference potential to avoid digital noise coupling.

[0115] In some embodiments, such as Figure 6 As shown, the discrimination comparator module includes:

[0116] Operational amplifier U8; A parallel filter resistor R38 and filter capacitor C40 are connected to the third interface terminal of operational amplifier U8; the parallel filter resistor R38 and filter capacitor C40 are further connected to the second interface terminal of operational amplifier U8 and grounded; the other end of filter capacitor C40 is connected to the preceding circuit, for example, to the output current limiting resistor R35 of the voltage amplifier module; an amplification resistor R42 is connected to the fourth interface terminal of operational amplifier U8, and the amplification resistor R42 is further connected to the second interface terminal of operational amplifier U8; a filter shaping resistor R36 is connected to the first interface terminal of operational amplifier U8. The filtering shaping resistor R36 is connected to the filtering shaping capacitor C41, which is further connected to the second interface terminal of the operational amplifier. A connection is established between the filtering shaping resistor R36 and the filtering shaping capacitor C41 to the subsequent stage circuit, transmitting the shaped and stable radiated signal to the subsequent stage circuit. The fifth interface terminal of the operational amplifier U8 is connected to the amplification resistor R30 and the power supply filter capacitor C32, which is further grounded. The amplification resistor R30 is further connected to the fourth interface terminal of the operational amplifier U8. A power supply VCC_3V3A is connected between the amplification resistor R30 and the power supply filter capacitor C32.

[0117] Typically, the discrimination comparator module based on operational amplifier U8, which can be a TLV3201AIDBVR, is used for amplifying, filtering, and shaping weak radiation signals, converting the small-amplitude, easily interfered-prone signal output by the detector into a stable, processable signal. The TLV3201's high bandwidth adapts to the narrow pulse characteristics of the radiation signal, ensuring no distortion during signal amplification. A filtering network consisting of filter capacitor C40, power supply filter capacitor C32, and filter shaping capacitor C41 achieves end-to-end noise suppression, preventing the masking of weak radiation signals. Filter resistor R38 matches the detector output impedance, reducing signal reflection and attenuation, and ensuring signal integrity. The operational amplifier U8 uses the high-speed, low-noise, rail-to-rail output operational amplifier TLV3201AIDBVR as its core component. It boasts high bandwidth (suitable for fast pulse signals) and low offset voltage, effectively amplifying the weak pulse or current signals output by the radiation detector while suppressing noise and ensuring signal quality. The filter resistor R38 and filter capacitor C40 (33pF) form an RC filter network to remove high-frequency noise from the input signal and achieve impedance matching, resulting in a cleaner signal input to the op-amp. The amplification resistors R42 (9.3KΩ) and R30 (100KΩ) together with the operational amplifier U8 form a non-inverting amplifier circuit, amplifying the weak signal output by the radiation detector to a suitable amplitude. The circuitry is designed to facilitate identification and processing by subsequent circuitry. A power supply filter capacitor C32 (0.1μF) filters out high-frequency noise on the power line, ensuring a clean operating power supply for the op-amp and preventing noise coupling into the signal path, thus affecting the amplification accuracy of the radiated signal. A filter shaping resistor R36 (33Ω) and a filter shaping capacitor C41 (5.6nF) form an RC output filter / shaping network, further filtering the amplified signal and adjusting the rise / fall times to make the output signal closer to an ideal pulse, facilitating accurate acquisition of radiated events by subsequent circuitry. The TP6 test point is set before the subsequent circuitry to measure the amplified signal waveform and verify circuit performance. CON connects to the subsequent circuitry, transmitting the conditioned and stable radiated signal.

[0118] Some embodiments of the portable neutron personal dosimeter disclose a power supply circuit unit including a buck circuit module, a boost circuit module, a storage circuit module, and a switch control circuit module.

[0119] In some embodiments, such as Figure 7 As shown, the step-down circuit module includes:

[0120] DC-DC converter U1; the first interface terminal (EN) and the fourth interface terminal (IN) of DC-DC converter U1 are connected, and the second interface terminal (GND) of DC-DC converter U1 is grounded; an input filter capacitor C1 is connected in parallel between the second interface terminal (GND) and the first interface terminal (EN) of DC-DC converter U1; the input filter capacitor, the first interface terminal (EN), and the fourth interface terminal (IN) are further connected to the input voltage terminal VCC_BAT; the third interface terminal (LX) of DC-DC converter U1 is connected to inductor L1, and inductor L1 is further connected to one end of the feedback and output regulation resistor R4, and the output filter capacitors C2, C3, and C4 in sequence, and is further connected to the output voltage terminal VCC_3V. 3. Connections: A feedback and output regulation resistor R7 is connected between the fifth interface terminal (FB) and the second interface terminal (GND) of the DC-DC converter U1. The fifth interface terminal (FB) is further connected to the other end of the feedback and output regulation resistor R4 and the other end of the output filter capacitor C2. The other ends of the output filter capacitors C3 and C4 are grounded. The two ends of the output filter capacitor C4 are further connected to the two ends of the protection diode D1 respectively. Test point TP1 is set at the connection between the first interface terminal (EN) and the fourth interface terminal (IN) of the DC-DC converter U1. Test points TP2 and TP4 are set at the two ends of the protection diode D1 respectively.

[0121] Typically, a buck converter module is a functional module based on a DC-DC buck converter. It constructs an efficient buck topology using the DC-DC buck converter, and, in conjunction with filtering, feedback, and protection components, achieves a stable 3.3V output from the input voltage. This meets the power supply requirements for low noise and high reliability, ensuring accurate and stable voltage for clock circuits, storage circuits, MCUs, and communication circuits. The DC-DC buck converter can utilize the SY8088 high-frequency synchronous buck DC-DC converter, which integrates a power MOSFET, supports efficient voltage conversion, and can stably output the target voltage over a wide input voltage range.

[0122] In the buck converter module, the input filter capacitor C1 is connected in parallel between the input voltage VCC_BAT and ground to filter out high-frequency noise in the input voltage, making the voltage input to the chip cleaner. This also helps stabilize the chip's operation and avoids voltage fluctuations interfering with the conversion process. The inductor L1 (2.2μH) and the switching node are key components of the DC-DC buck converter circuit. When the internal switch is on, the inductor stores energy; when the switch is off, the inductor releases energy through freewheeling, working with the internal circuitry to achieve voltage buck conversion. Its inductance value is selected to match parameters such as input / output voltage and load current to ensure conversion efficiency and stability. The LX pin is the switching node of the DC-DC buck converter chip, connected to the inductor, reflecting the operating state of the internal switch. Externally, a buck topology is constructed using inductors and capacitors.

[0123] The feedback and output regulation resistors R4 (115K) and R7 (25.5K) form a voltage divider feedback network, which is connected to the feedback (FB pin) of the DC-DC buck converter chip. After the output voltage VCC_3V3 is divided, it is fed back to the chip and compared with the internal reference voltage. The chip adjusts the on-time of the switching transistor accordingly to stabilize the output voltage of 3.3V.

[0124] Output filter capacitors C2 (33pF), C3 (22μF), and C4 (0.1μF) are connected in parallel between the output VCC_3V3 and ground, forming the output filter capacitor group. Small-value capacitors (such as C2 and C4) mainly filter out high-frequency noise, have a fast response speed, and suppress ripple caused by the switching frequency. Large-value capacitors (such as C3) are responsible for bulk filtering, stabilizing the DC component of the output voltage, and coping with voltage fluctuations when the load current changes, making the output smoother.

[0125] The protection diode D1 is an electrostatic discharge protection component, which can be CESD3V3D3 YU; it is connected in parallel between the output VCC_3V3 and ground; when the circuit encounters abnormal high voltage such as static electricity or surge, the protection diode D1 conducts, clamping the overvoltage within a safe range and protecting the downstream load U circuit from damage; test points TP1, TP2, and TP4 are used to measure the voltage and waveform of the corresponding nodes with an oscilloscope and multimeter during debugging and maintenance. For example, TP1 measures the input voltage, TP2 measures the output voltage, and TP4 measures ground or performs auxiliary testing to quickly determine whether the circuit is working properly.

[0126] In some embodiments, such as Figure 8 As shown, the boost circuit module includes:

[0127] Boost converter U3; an inductor L2 is connected between the VIN and SW interfaces of boost converter U3; the EN interface of boost converter U3 is connected to one end of resistor R11, and inductor L2 is connected to the other end of resistor R11, further connected to the input voltage terminal VCC_BAT; an input filter capacitor C6 is connected between the GND terminal of boost converter U3 and the input voltage terminal VCC_BAT, and the input filter capacitor C6 and the GND terminal of boost converter U3 are grounded; the SW interface of boost converter U3... Further configuration involves connecting diode D2, output filter capacitors C9 and C10 in sequence; the FB interface of boost converter U3 is connected to output adjustment resistors R12 and R15, with the other end of output adjustment resistor R12 connected between diode D2 and output filter capacitor C9, and the other end of output adjustment resistor R15 grounded to GND and connected to the other ends of output filter capacitors C9 and C10; the output terminal of diode D2 outputs a boosted DC voltage VCC_12V; a test point TP3 is also provided at the output terminal of diode D2;

[0128] The voltage regulator U2 has the following interface terminals: First and third interface terminals are connected, and further connected to a DC voltage VCC_12V; Second interface terminal is grounded; Input filter capacitor C11 is connected in parallel between the second and first interface terminals; Fourth interface terminal is connected to output regulating resistors R13, R14, and R16; Fifth interface terminal is sequentially connected to the other end of output regulating resistor R13 and one end of output filter capacitors C7 and C8; The other end of output regulating resistor R16 is connected to the second interface terminal; The other end of output regulating resistor R14 is connected to the other end of output filter capacitor C7, and the other end of output filter capacitor C8 is connected to the other end of output regulating resistor R16; The fifth interface terminal of the voltage regulator U2 ultimately outputs a stepped-down regulated DC voltage VCC_10V, and a test point TP5 is also provided on the fifth interface terminal.

[0129] Typically, a boost converter module is a power supply system consisting of two stages of DC-DC conversion circuits, which respectively implement boost and linear regulation functions to meet the requirement of stable output from low input voltage to 10V, while taking into account certain noise suppression and voltage accuracy, providing a stable voltage for silicon semiconductor detectors. The first stage is the boost circuit based on boost converter U3 (MT3608 can be used); the core chip MT3608 is a commonly used boost converter with a built-in power switch, achieving low input voltage boost through PWM control; VCC_BAT is the input voltage, and the input filter capacitor C6 (22μF) filters out high-frequency noise in the input voltage to stabilize the input; inductor L2 is a key component of the boost circuit, storing energy when the switch is on and releasing energy through the freewheeling diode when it is off, thus achieving voltage boost; diode D2 (B0505WS can be used) acts as a freewheeling element, providing current to the inductor when the switch is off. The circuit ensures energy transfer to the output terminal while using unidirectional conductivity to prevent reverse current flow of the output voltage; feedback and output regulation: R3 (100K) and R4 (2.5K) form a voltage divider feedback network, connected to the FB pin of the boost converter chip; the output voltage VCC_12V is divided and fed back to the chip, compared with the reference voltage, and the chip adjusts the duty cycle of the switching transistor to stabilize the output 12V voltage; output filter capacitors C9 (10μF) and C10 (0.1μF) filter out the high-frequency ripple after boosting, making the output VCC_12V smoother; test point TP1 is used to measure the VCC_12V voltage or waveform for convenient debugging and testing;

[0130] The second stage is the linear voltage regulator circuit based on voltage regulator converter U2. Voltage regulator converter U2 uses the CAT4139JT chip. The CAT4139JT is a linear voltage regulator (LDO) used to stably step down a 12V input to a 10V output. It features low noise and high linear regulation and is used to power silicon semiconductor detectors.

[0131] The input filter capacitor C11 (2.2μF) is used for input filtering to further filter out the residual ripple of the 12V voltage in the previous stage and ensure that the voltage input to the LDO is pure. The output filter capacitors C7 (1μF) and C8 (1μF) are used for output filtering to suppress low-frequency noise in the LDO output and stabilize the 10V output voltage.

[0132] Output regulating resistors R13 (110k) and R14 (10k) are used to set the output current limit or to cooperate with the internal circuit of the chip to realize current detection; output regulating resistor R16 (15K) combined with the internal structure of the chip may participate in voltage feedback or bias setting to ensure stable 10V output.

[0133] Test points TP3 and TP5 are used to measure voltage or waveform to assist in debugging and verifying whether the output is normal.

[0134] In some embodiments, such as Figure 9 As shown, the storage circuit module includes:

[0135] Erasable Programmable Read-Only Memory U4; the first interface terminal A0, the second interface terminal A1, the third interface terminal A2, and the fourth interface terminal GND of the erasable programmable read-only memory U4 are connected and grounded; the eighth interface terminal VCC of the erasable programmable read-only memory U4 is connected to the VCC_3V3 power supply; the seventh interface terminal WP of the erasable programmable read-only memory U4 is grounded; the sixth interface terminal SCL of the erasable programmable read-only memory U4 is connected to the I2C_SCL of the system bus; the fifth interface terminal SDA of the erasable programmable read-only memory U4 is connected to the system data line I2C_SDA.

[0136] Typically, the storage circuit module is a storage circuit module based on electrically erasable programmable read-only memory (EEPROM) to realize "microcontroller ← I 2 The data storage link “C bus → AT24C64EEPROM” is used to implement non-volatile data storage in the system;

[0137] Electrically erasable programmable read-only memory (EEPROM) can be used with I... 2 The AT24C64 with a C interface has a capacity of 64Kbit (8KB) ​​and supports operation at 2.5V-5.5V. It connects via I... 2 The C-bus communicates with the microcontroller to write and read data, storing configuration parameters, logs, and data that needs to be saved when power is off. The eighth interface terminal, VCC, is connected to the system's 3.3V power supply to power the chip; the fourth interface terminal, GND, is used for grounding and providing a reference potential; the fifth interface terminal connects to the system I-channel. 2 The I2C_SCL connection on the C bus, where SCL is the I2C bus connection. 2 C is the clock line, transmitting clock signals and synchronizing data transmission and reception; SDA is I 2 The C data line connects to the system I2C_SDA and is used for reading and writing commands, storing content, etc.; the address pins include A0, A1, A2, and I... 2 The slave address setting pin (C) is grounded to GND in this circuit, therefore the I of the AT24C64... 2 The slave address is fixed by hardware.

[0138] WP is the write protection control pin; I 2 The C bus protocol requires SCL and SDA to be open-drain (or open-collector) outputs, typically requiring external pull-up resistors R18 and R19 connected to the power supply to pull the levels high when the bus is idle, ensuring normal communication logic. Generally, I... 2C-bus pull-up resistors R18 (4.7KΩ) and R19 (4.7KΩ).

[0139] I2C_SCL and I2C_SDA can be used as test points to easily capture bus waveforms with an oscilloscope or logic analyzer and debug communication faults.

[0140] Some embodiments of the portable neutron personal dosimeter disclosed also include a main unit housing and a back clip; such as Figure 10 As shown, the main unit housing includes an upper housing 2 and a lower housing 1, made of ABS engineering plastic, which has good plasticity, thermal properties, and chemical stability, with a density of only 1.18 g / cm3, making it both lightweight and structurally strong. The upper and lower edges and the left side wall of the main unit housing all feature a large arc design, eliminating sharp edges. A display screen 5 is mounted on the upper housing 2, with a first button 6 and a second button 7 located below it. A through-hole is provided above the display screen 5 for placing a buzzer 4 and an indicator light 3. A battery cover 8 is located on the right side of the main housing for inserting and removing the battery; the edge of the battery cover is sealed with a silicone O-ring for added waterproofing.

[0141] Typically, the main housing has sealed edges and an internal anti-electromagnetic interference coating to reduce electromagnetic interference. The seam between the upper and lower housings is sealed with a silicone O-ring for added water resistance. The silicon semiconductor detector and nuclear electronics circuitry are housed within the main housing. Optimized internal structure achieves lightweight portability. The button consists of two buttons, offering a simple and easy-to-use operation. A membrane button is used to switch between real-time / cumulative dose rate display functions, parameter setting menus, and power on / off operation. The display is an OLED screen with high brightness and contrast, ensuring clear data display in both bright light and low-light conditions. It features a short response time for real-time content display. A 14500 rechargeable lithium battery is used to achieve lightweight portability.

[0142] In some embodiments, such as Figure 11 As shown, the switch control circuit module includes:

[0143] MOSFET Q3; the source-base (S) of MOSFET Q3 is connected to BAT+, and the drain (D) is connected to VCC_BAT, which can be further connected to the subsequent load. A resistor R2 is connected in parallel between the gate (G) and the source-base (S); the gate (G) of MOSFET Q3 is further connected to the first interface terminal of Schottky diode Q2 and the drain (D) of MOSFET Q4, respectively; the voltage at the gate (G) of MOSFET Q3 controls its on / off state.

[0144] The second interface terminal of the Schottky diode Q2 is connected to a pull-up resistor R1, which is further connected to the VCC_3V3 power supply. The third interface terminal of the Schottky diode Q2 is connected to the second interface terminal of the membrane key K2. The Schottky diode Q2 acts as a rectifier to prevent voltage fluctuations in the circuit and achieve unidirectional conduction in the current path.

[0145] The source S of the MOS field-effect transistor Q4 is grounded to GND, and a pull-down resistor R10 and a current-limiting resistor R8 are connected between the source S and the gate G of the MOS field-effect transistor Q4.

[0146] The point between the pull-down resistor R10 and the current-limiting resistor R8 is the PWC point, and the point between the second interface terminal of the Schottky diode Q2 and the resistor R1 is the PWT point. Typically, the switch control circuit module controls the MOSFET switching circuit of the battery power supply through digital signals. It utilizes the complementary characteristics of P-channel and N-channel MOSFETs, along with diodes and resistors, to achieve level logic conversion and power control.

[0147] Figure 11 In the diagram, Q3 is a P-channel MOSFET, which can be an AO3401A, used as the main power switch. Its source (S) is connected to the battery power supply BAT+, and its drain (D) can be connected to the subsequent load through VCC_BAT. Its turn-on / off is controlled by the gate (G) voltage: when the G voltage is lower than a certain threshold at the S, Q3 turns on, and VCC_BAT supplies power to the subsequent stage; otherwise, it turns off. Q4 is an N-channel MOSFET, used as a control switch. An AO3400 can be used in conjunction with Q3 to achieve gate level control. The N-channel characteristic is that it turns on when the G voltage is higher than a certain threshold at the S. Q2 is a Schottky diode, which can be a BAT54C, used for level clamping and logic conversion. Its positive... The conduction voltage drop adjusts the node level; R1 (100K) is a pull-up resistor, which pulls the gate of Q3 to VCC_3V3 when Q4 is turned off, ensuring reliable turn-off of Q3 and avoiding false turn-on due to gate floating; R8 (10K) is a current-limiting resistor, which provides appropriate drive current to the gate of Q4 and prevents excessive current from damaging the gate of Q4 when the PWC level is abnormal; R10 (100K) is a pull-down resistor, which provides stable ground potential to the source of Q4 and ensures the accuracy of gate level detection of Q4; Q2 (BAT54C): Schottky diode, which uses its unidirectional conduction characteristic to assist in controlling the level state of the control circuit and ensure that the components operate within a safe and appropriate voltage range.

[0148] The working logic of the switch control circuit mainly has two states.

[0149] State 1: PWC is low.

[0150] PWC low → Q4 gate voltage low → Q4 (N-channel) turns off; Q3 gate level is pulled up by R1, VCC_3V3 goes through R1 (100K) to the PWT node, and then through the internal diode of Q2 to the gate of Q3 → Q3 gate voltage is close to VCC_3V3; Q3 is P-channel, the source is connected to VCC_BAT, the gate voltage is close to VCC_3V3. If VCC_BAT and VCC_3V3 voltages are close, the gate voltage and source voltage difference is small, Q3 turns off → the subsequent load has no VCC_BAT power supply.

[0151] State 2: PWC is high.

[0152] PWC high → applied to the gate (G) of Q4 via R8 (10K) → Q4 (N-channel) conducts; after Q4 conducts, the gate (G) of Q3 is grounded through Q4 → the gate voltage of Q3 becomes low; Q3 is a P-channel, its source (S) is connected to VCC_BAT, and its gate voltage is low → satisfying the P-channel conduction condition → Q3 conducts → VCC_BAT supplies power to the subsequent stage.

[0153] Typically, the button circuit module employs a button debouncing input circuit. Utilizing the mechanical structure of the four-pin button and a filtering capacitor, it converts button presses into stable level signals for detection by the main control system. The button module includes two membrane buttons, K1 and K2, for functions such as power on / off, parameter setting, and function setting.

[0154] In some embodiments, such as Figure 12 As shown, the button circuit module includes:

[0155] A membrane key K1 has a filter capacitor C16 connected in parallel between its second and third interface terminals; a fourth interface terminal is connected to the third interface terminal; a key K1 is configured on the first and second interface terminals; the second terminal of the membrane key K1 is further used to connect to the switch control circuit of K1.

[0156] Membrane button K2 has its third and fourth interface terminals connected and a parallel filter capacitor C17 connected to its first interface terminal. The first and fourth interface terminals of membrane button K2 are used to set up button K2. The third and fourth interface terminals of membrane button K1 and membrane button K2 are grounded (GND). The second interface terminal of membrane button K2 is used to connect to the switch control circuit of K2.

[0157] When the button is not pressed, the internal contacts of the button are open, and the button signal terminal is kept at a high level through the filter capacitors C16 and C17; when the button is pressed, the internal contacts of the button are closed, the button signal terminal is directly grounded, the level becomes low, and the main controller detects the button action.

[0158] Filter capacitors C16 and C17 (10nF, ceramic capacitors) are debounce capacitors. When a button is pressed / released, the mechanical contacts may briefly jitter, causing a rapid change in voltage level, which may be misinterpreted by the main controller as multiple button presses. The capacitors "smooth" the voltage level change through charging and discharging, absorbing the spike noise generated by the jitter, ensuring that the main controller detects a stable low level (pressed) or high level (released), thus achieving the "debounce" function.

[0159] In some embodiments, the information processing unit includes a microcontroller. Typically, the information processing unit includes a microcontroller (MCU) and peripheral control and debugging interface circuitry. For example, a minimum microcontroller system based on the FM33LG045 integrates power supply, clock, debugging, communication, and general-purpose I / O. The debugging and communication interface circuitry is a combined "SWD debugging + UART serial port" interface, accommodating both program development debugging and serial communication needs. The MCU needs to process and calculate the dose rate and cumulative dose from the acquired sensor signals. In some embodiments, the MCU is a 64MHz ARM Cortex-M0+ low-power processor, 256kB flash memory, 32kBSRAM, and rich interfaces and peripherals. Typical operating power consumption is 30130μA / MHz@48MHz. It has a built-in display driver module for driving OLED LCD screens, supporting 4, 6, and 8 COM, with maximum display segments of 176 segments (4COM), 252 segments (6COM), and 320 segments (8COM), respectively.

[0160] In addition, through the interconnected control of various components, functions such as audible and visual alarms for exceeding dose rate thresholds and cumulative dose storage are achieved. The device records the dose rate of the current environment in real time, refreshing the data every 2 seconds. When the dose rate exceeds the preset threshold, the device will issue a visual and audible alarm and display the alarm information on the screen. The device has the function of recording the cumulative dose rate, from zero to the current moment.

[0161] The portable neutron personal dosimeter disclosed in this invention has a simple structure, is easy to use, and can accurately detect neutron radiation, providing good protection for individuals. It has good application prospects in the field of neutron detection.

[0162] The technical solutions and technical details disclosed in the embodiments of this invention are merely illustrative of the inventive concept of this invention and do not constitute a limitation on the technical solutions of the embodiments of this invention. Any conventional changes, substitutions, or combinations made to the technical details disclosed in the embodiments of this invention have the same inventive concept as this invention and are within the protection scope of the claims of this invention.

Claims

1. A portable neutron personal dosimeter, characterized in that, include: A silicon semiconductor detector unit is used to detect neutron radiation and generate a corresponding electrical signal; A preamplifier circuit unit, connected to the silicon semiconductor detector unit, is used to process the detected neutron radiation signal and convert it into a pulse signal. The preamplifier circuit unit includes: a preamplifier module for amplifying the neutron radiation signal; a shaping filter module for filtering the amplified neutron radiation signal; a voltage amplifier module for amplifying the filtered radiation signal; and a discrimination comparator module for converting the amplified neutron radiation signal into a stable radiation signal. An information processing unit, configured to be connected to the preamplifier circuit unit, is used to process pulse signals and output neutron dose information; A power supply circuit unit is used to provide suitable voltages to the silicon semiconductor detector unit, the preamplifier circuit unit, and the information processing unit, respectively. The display screen unit is connected to the information processing unit and is used to display neutron dose information; An alarm unit is configured to be connected to the information processing unit and is used to output an alarm signal; The preamplifier module includes an operational amplifier (U6); the fifth and sixth interfaces of the operational amplifier (U6) are connected, and further connected to a power filter bead (FB1), which is further connected to a VCC_3V3A power supply; parallel power filter capacitors (C24, C25, C26) are connected to the fifth and sixth interfaces of the operational amplifier (U6), and these parallel power filter capacitors (C24, C25, C26) are grounded; the third interface of the operational amplifier (U6) is connected to an electrostatic protection diode (D5) and a feedback resistor (R28). The source of the field-effect transistor (Q7) is connected in sequence; the other end of the feedback resistor (R28) is connected to the VCC_3V3A power supply; the electrostatic protection diode (D5) is further grounded; the drain of the field-effect transistor (Q7) is connected to a parallel resistor (R43) and capacitor (C44), and the other end of the parallel resistor (R43) and capacitor (C44) is grounded; the fourth interface terminal of the operational amplifier (U6) is connected to a parallel compensation filter capacitor (C39) and compensation filter resistor (R37), and the parallel compensation filter capacitor (C39) and compensation filter resistor (R37) are further connected to the second interface terminal of the operational amplifier (U6). The operational amplifier (U6) is connected and grounded; a feedback resistor (R29) is also connected to the fourth interface terminal of the operational amplifier (U6), and the other end of the feedback resistor (R29) is connected to the fifth and sixth interface terminals of the operational amplifier (U6); the gate of the field-effect transistor (Q7) is connected to a parallel phase compensation resistor (R26) and a phase compensation capacitor (C30), and the parallel phase compensation resistor (R26) and phase compensation capacitor (C30) are further connected to the first interface terminal of the operational amplifier (U6); the gate of the field-effect transistor (Q7) is further connected to a DC blocking capacitor (C35), and the DC blocking capacitor (C35) is further... The voltage divider and current limiting resistors (R31 and R27) and the VCCA_10V power supply are connected in sequence. A coaxial interface (J2) is provided between the DC blocking coupling capacitor (C35) and the voltage divider and current limiting resistor (R31), and the coaxial interface (J2) is grounded. An input filter capacitor (C29) is provided between the voltage divider and current limiting resistor (R31) and the voltage divider and current limiting resistor (R27), and the input filter capacitor (C27) is further grounded. An input filter capacitor (C27) is provided between the voltage divider and current limiting resistor (R27) and the VCCA_10V power supply, and the input filter capacitor (C27) is further grounded. The shaping filter module includes: an operational amplifier (U7A); a power filter bead (FB2) is connected to the eighth interface of the operational amplifier (U7A), and the power filter bead (FB2) is further connected to a VCC_3V3A power supply; the eighth interface of the operational amplifier (U7A) is also connected to parallel power filter capacitors (C28, C31), and the parallel power filter capacitors (C28, C31) are further grounded; the third interface of the operational amplifier (U7A) is configured for phase compensation / filtering. A capacitor (C38), a voltage divider and current limiting resistor (R34), a high-frequency filter capacitor (C37), a voltage divider and current limiting surge resistor (R33), a filter capacitor (C33), and a filter resistor (R32) are connected in sequence; the phase compensation / filter capacitor (C38) is further grounded; a resistor (R40) and a capacitor (C36) are connected between the voltage divider and current limiting resistor (R33) and the filter capacitor (C33), and the resistor (R40) is further grounded; a feedback resistor (R44) is connected to the second interface terminal of the operational amplifier (U7A). R47); the feedback resistor (R47) is further grounded; the feedback resistor (R44) is further connected to the feedback resistor (R45); the feedback resistor (R45) is further connected to the first interface terminal of the operational amplifier (U7A); the high-frequency filter capacitor (C37) is further connected between the feedback resistor (R44) and the feedback resistor (R45); the first interface terminal of the operational amplifier (U7A) is further connected to the capacitor (C34); the capacitor (C34) is further connected to the parallel phase compensation capacitor (C42) and the phase compensation resistor (R41); the other end of the parallel phase compensation capacitor (C42) and the phase compensation resistor (R41) is grounded; The voltage amplifier module includes: an operational amplifier (U7B); the fifth interface of the operational amplifier (U7B) is configured to connect to the preamplifier circuit; the sixth interface of the operational amplifier (U7B) is configured to be connected with a parallel feedback resistor (R39) and a phase compensation capacitor (C43), and is further configured to be sequentially connected to an input current limiting / bias resistor (R46) and an input filter capacitor (C45), the input filter capacitor (C45) being further grounded; the parallel feedback resistor (R39) and the phase compensation capacitor (C43) are further configured to be connected to the seventh interface of the operational amplifier (U7B); the seventh interface of the operational amplifier (U7B) is further configured to be connected with an output current limiting resistor (R35). The discrimination comparator module includes: an operational amplifier (U8); a parallel filter resistor R38 and a filter capacitor (C40) are connected to the third interface terminal of the operational amplifier (U8); the parallel filter resistor (R38) and the filter capacitor (C40) are further connected to the second interface terminal of the operational amplifier (U8) and grounded; the operational amplifier (U8) The fourth interface terminal of the operational amplifier (U8) is connected to an amplification resistor (R42), which is further connected to the second interface terminal of the operational amplifier (U8). The first interface terminal of the operational amplifier (U8) is connected to a filter shaping resistor (R36), which is connected to a filter shaping capacitor (C41). The filter shaping capacitor (C41) is further connected to the second interface terminal of the operational amplifier (U8). The filter shaping resistor (R36) and the filter shaping capacitor (C41) are connected to a subsequent stage circuit to transmit the shaped and stable radiated signal to the subsequent stage circuit. The fifth interface terminal of the operational amplifier (U8) is connected to an amplification resistor (R30) and a power supply filter capacitor (C32). The power supply filter capacitor (C32) is further grounded, and the amplification resistor (R30) is further connected to the fourth interface terminal of the operational amplifier (U8). A VCC_3V3A power supply is connected between the amplification resistor (R30) and the power supply filter capacitor (C32).

2. The portable neutron personal dosimeter according to claim 1, characterized in that, The power supply circuit unit includes a buck circuit module, a boost circuit module, a storage circuit module, a switch control circuit module, a button circuit module, and a display interface circuit module.

3. The portable neutron personal dosimeter according to claim 2, characterized in that, The step-down circuit module includes: DC-DC converter (U1); The first and fourth interface terminals of the DC-DC converter (U1) are connected, and the second interface terminal of the DC-DC converter (U1) is grounded; an input filter capacitor (C1) is connected in parallel between the second interface terminal and the first interface terminal of the DC-DC converter (U1); the input filter capacitor (C1), the first interface terminal, and the fourth interface terminal are further connected to the input voltage terminal VCC_BAT. The third interface terminal of the DC-DC converter (U1) is connected to the inductor (L1), and the inductor (L1) is further connected to one end of the feedback and output regulation resistor (R4) and the output filter capacitor (C2, C3, C4) in sequence, and is further connected to the output voltage terminal VCC_3V3. A feedback and output regulation resistor (R7) is provided between the fifth interface terminal and the second interface terminal of the DC-DC converter (U1). The fifth interface terminal is further connected to the other end of the feedback and output regulation resistor (R4) and the other end of the output filter capacitor (C2). The other end of the output filter capacitor (C3, C4) is grounded. The two ends of the output filter capacitor (C4) are further connected to the two ends of the protection diode (D1).

4. The portable neutron personal dosimeter according to claim 2, characterized in that, The boost circuit module includes: Boost converter (U3); An inductor (L2) is connected between the VIN and SW interfaces of the boost converter (U3); the EN interface of the boost converter (U3) is connected to one end of a resistor (R11), the inductor (L2) is connected to the other end of the resistor (R11), and is further connected to the input voltage terminal VCC_BAT. An input filter capacitor (C6) is connected between the GND terminal of the boost converter (U3) and the input voltage terminal VCC_BAT. The input filter capacitor (C6) and the GND terminal of the boost converter (U3) are grounded. The SW interface of the boost converter (U3) is further connected to a diode (D2) and output filter capacitors (C9, C10) in sequence; the FB interface of the boost converter (U3) is connected to an output regulating resistor (R12, R15), the other end of the output regulating resistor (R12) is connected between the diode (D2) and the output filter capacitor (C9), and the other end of the output regulating resistor (R15) is grounded (GND) and connected to the other end of the output filter capacitors (C9, C10); the output terminal of the diode (D2) outputs a boosted DC voltage VCC_12V; Zener converter (U2); The first interface terminal of the voltage regulator (U2) is connected to the third interface terminal, and further connected to the DC voltage VCC_12V; the second interface terminal of the voltage regulator (U2) is grounded; an input filter capacitor (C11) is connected in parallel between the second interface terminal and the first interface terminal of the voltage regulator (U2). The fourth interface of the voltage regulator (U2) is connected to an output regulating resistor (R13, R14, R16); the fifth interface of the voltage regulator (U2) is sequentially connected to the other end of the output regulating resistor (R13) and one end of the output filter capacitor (C7, C8); the other end of the output regulating resistor (R16) is connected to the second interface of the voltage regulator (U2); the other end of the output regulating resistor (R14) is connected to the other end of the output filter capacitor (C7), and the other end of the output filter capacitor (C8) is connected to the other end of the output regulating resistor (R16); the fifth interface of the voltage regulator (U2) finally outputs a DC voltage VCC_10V after step-down regulation.

5. The portable neutron personal dosimeter according to claim 2, characterized in that, The storage circuit module includes: Erasable programmable read-only memory (U4); The first, second, third, and fourth interface terminals of the erasable programmable read-only memory (U4) are connected and grounded; The eighth interface of the erasable programmable read-only memory (U4) is connected to a VCC_3V3 power supply. The seventh interface terminal of the erasable programmable read-only memory (U4) is grounded; The sixth interface of the erasable programmable read-only memory (U4) is configured to be connected to the I2C_SCL of the system bus; The fifth interface of the erasable programmable read-only memory (U4) is configured to connect to the system data line I2C_SDA.

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