A wideband radio frequency sampling method and apparatus

Abstract

The application relates to the technical field of radio frequency signal processing, and discloses a wideband radio frequency sampling method and device, wherein the method comprises the following steps: constructing a composite pilot injection path; extracting the time sequence deviation of each channel; performing delay compensation and frequency domain distortion extraction; sequentially performing amplitude and phase frequency domain compensation; evaluating the spurious-free dynamic range based on a correction signal sequence; and outputting a radio frequency sampling reference signal sequence. Compared with the prior art, the method can solve the technical problem that it is difficult to realize the cooperative calibration of cross-channel time sequence, bandwidth and gain in a temperature drift and power disturbance environment under a multi-path interleaving structure, especially under the conditions of a Sub-6GHz to 7GHz multi-carrier direct sampling of a 6G prototype base station and a bandwidth aggregation of 400MHz and above, and it is difficult to realize stable spurious-free dynamic range performance guarantee. Due to the composite pilot injection, double-domain error estimation and SFDR feedback calibration mechanism, the dynamic range and distortion suppression performance under the condition of wideband radio frequency direct sampling are improved.

Description

Technical Field

[0001] This invention relates to the field of radio frequency signal processing technology, and in particular to a broadband radio frequency sampling method and apparatus. Background Technology

[0002] Currently, with the ever-increasing demands for data transmission rates, spectral efficiency, and system reliability from 5G and future 6G communication systems, radio frequency (RF) signal sampling technology faces unprecedented challenges. In modern communication systems, especially in high-bandwidth, multi-carrier aggregation environments, traditional analog-to-digital converter (ADC) technologies often fail to meet the requirements of high precision and high dynamic range when processing broadband signals. While existing multi-interleaved ADC structures can improve sampling rates and reduce power consumption to some extent, several technical bottlenecks still exist in practical applications. For example, in broadband RF signal sampling in the Sub-6 GHz to 7.125 GHz bands, the timing mismatch, gain imbalance, and bandwidth mismatch problems of interleaved ADCs are particularly severe due to changes in environmental factors such as temperature variations, power supply disturbances, and clock skew. These mismatches not only lead to spectral distortion and signal reconstruction errors but also seriously affect the spurious-free dynamic range (SFDR) index, limiting the system's performance in high dynamic range and high-precision applications. Existing technologies typically rely on single pilot injection or offline calibration techniques. Although these methods can provide some compensation in static environments, they cannot adapt to complex dynamic environments in real time. For example, when the system operates under conditions of high temperature drift or power supply ripple interference, existing technologies cannot perform real-time adaptive calibration quickly and accurately, which leads to a decrease in the accuracy of the sampling system, increased distortion, and even signal loss.

[0003] Therefore, there is an urgent need for a broadband radio frequency sampling method that can stably provide optimized sampling results under the requirements of high precision and high dynamic range in broadband signal sampling. Especially in the multi-carrier aggregation and high-frequency broadband sampling scenarios of 6G communication systems, the new sampling method must be able to eliminate distortion, improve dynamic range, and converge quickly to meet the needs of real-time, continuous, and high-quality data processing. Summary of the Invention

[0004] To address the aforementioned technical shortcomings, the purpose of this invention is to propose a broadband radio frequency sampling method that aims to solve the technical problem of difficulty in achieving coordinated calibration of cross-channel timing, bandwidth, and gain under multi-interleaved structures and in environments with temperature drift and power supply disturbances. This is especially true under the conditions of direct sampling of multiple carriers from Sub-6GHz to 7GHz and bandwidth aggregation of 400MHz and above in 6G prototype base stations, where it is difficult to achieve stable spurious dynamic range performance assurance.

[0005] To solve the above-mentioned technical problems, the present invention adopts the following technical solution: The present invention provides a broadband radio frequency sampling method. The broadband radio frequency sampling method includes: Step S10: Acquire the multi-tone phase pilot signal at time t and sequence pilot signal Based on multi-tone phase pilot signals and sequence pilot signal Construct a composite pilot injection path; Step S20: Obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled, and perform time skew extraction processing on the interleaved sampling signal sequence using a multi-core correlation and frequency-assisted joint estimation mechanism based on the composite pilot injection path, and output the estimated time skew value. Step S30: Based on the time-series deviation estimate, perform delay compensation alignment and frequency domain distortion response extraction tasks on the interleaved sampled signal sequence, and output the frequency response deviation function. ; Step S40: Based on the frequency response deviation function For each sub-channel in the interleaved sampled signal sequence The output signal is sequentially processed by frequency domain amplitude compensation and phase compensation, and the output channel is aligned with the corrected signal sequence. Step S50: Based on the corrected signal sequence, process each sub-channel in the interleaved sampled signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the RF sampling reference signal sequence is finally output.

[0006] Preferably, in step S10, the multi-tone phase pilot signal ,in, This represents the amplitude of the k-th pilot frequency; This is the frequency of the k-th pilot signal; This is the phase of the k-th pilot. The number of pilot frequencies is determined by selecting a number that accounts for no less than 80% of the sampling bandwidth of Nyquist frequencies.

[0007] Preferably, step S20, which involves acquiring the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled, and performing time skew extraction processing on the interleaved sampling signal sequence using a multi-core correlation and frequency-assisted joint estimation mechanism based on the composite pilot injection path, and outputting the estimated time skew value, specifically includes: Step S201: Obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled. For each sub-channel in the interleaved sampling signal sequence... output signal Output signal of the preset reference channel The sliding cross-correlation calculation is performed using a sliding method with a windowed function to obtain the results for each sub-channel. Sliding cross-correlation score sequence Based on sliding cross-correlation score sequence The output time-domain estimate of the time corresponding to the peak position in the middle. Where n is the index of the sampling point; Step S202: Based on the multi-tone phase pilot signal The k-th pilot frequency is calculated using a differential phase extraction method based on spectrum analysis. The phase difference value is calculated, and a least-squares fitting method is used to perform linear slope fitting on the phase difference value, and the output is compared with the sub-channel. The corresponding frequency domain estimate ; Step S203: Based on time domain estimates and frequency domain estimates The timing bias estimate is calculated using a dynamic weighted fusion mechanism, and the sub-channel is output. Final time series bias estimate .

[0008] Preferably, in step S201, the sliding cross-correlation score sequence ,in, The length of the sliding window; This is the delay offset of the sliding cross-correlation; This indicates that the reference channel output signal is delayed in the time domain. Signal sample values ​​after each sampling point; The window function is a preset window function, including Hamming window, Kaiser window or cosine window, used to suppress edge effects with weights.

[0009] Preferably, in step S30, a delay compensation alignment task and a frequency domain distortion response extraction task are performed on the interleaved sampled signal sequence based on the time-series deviation estimate, and a frequency response deviation function is output. The steps specifically include: Step S301: First, perform a delay compensation alignment task on the interleaved sampled signal sequence based on the timing deviation estimate, utilizing each sub-channel. Corresponding time series deviation estimate Construct a compensation filter bank; Step S302: Then, based on the compensation filter bank, process each sub-channel in the interleaved sampled signal sequence. output signal Perform digital delay compensation and output aligned signal ; Step S303: Finally, for the aligned signals Perform a Discrete Fourier Transform (DFT) and, in conjunction with the frequency domain response of the reference channel corresponding to the preset reference channel output signal, extract each sub-channel. Frequency response deviation function .

[0010] Preferably, in step S40, the frequency domain amplitude compensation processing specifically includes: constructing a digital gain equalizer based on a preset amplitude deviation function, and correcting each sub-channel based on the digital gain equalizer. The amplitude response error of the output signal; frequency domain phase compensation processing specifically includes: constructing a phase equalization network based on an IIR filter based on a preset phase deviation function, and correcting and aligning each sub-channel based on the phase equalization network. The phase response of the output signal.

[0011] Preferably, in step S50, each sub-channel in the interleaved sampling signal sequence is processed based on the corrected signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the final output of the RF sampling reference signal sequence includes the following steps: Step S501: Based on the corrected signal sequence, process each sub-channel in the interleaved sampled signal sequence. The signal spectrum was calculated using the high-resolution spectral estimation method ESPRIT; the positions of the target dominant frequency component and non-dominant frequency components in the signal spectrum were identified, and the main lobe power corresponding to the target dominant frequency component position was obtained. Stray power corresponding to non-dominant frequency component positions Based on main lobe power Stray power corresponding to non-dominant frequency component positions Calculate each sub-channel Corresponding spurious-free dynamic range index , It also outputs a set of SFDR indicators; Step S502: Pre-set the indicator threshold value γ; when there is no spurious dynamic range indicator When the value is less than the preset threshold γ, the channel alignment correction signal sequence is determined to be invalid, and a dynamic amplitude injection and equalization feedback mechanism is triggered. The dynamic amplitude injection and equalization feedback mechanism specifically includes: Dynamic amplitude injection: superimposing a preset set of low-amplitude frequency domain pilot signals onto the sub-channel. Equalization feedback mechanism: After dynamic amplitude injection is completed, the frequency response deviation function is updated; when there is no spurious dynamic range index When the value is greater than or equal to the preset threshold value γ, the channel alignment correction signal sequence is determined to be valid, and the process proceeds directly to the next step. Step S503: For channels whose channel alignment correction signal sequence is valid, the correction signal sequence is output as the RF sampling reference signal sequence; for channels that trigger dynamic amplitude injection and equalization feedback mechanisms, the output signal is subjected to secondary correction processing according to the updated frequency response deviation function, including sequentially performing frequency domain amplitude compensation processing and phase compensation processing, and finally outputting the RF sampling reference signal sequence.

[0012] The present invention also provides a broadband radio frequency sampling device comprising: The pilot injection path construction module is used to acquire the multi-tone phase pilot signal at time t. and sequence pilot signal Based on multi-tone phase pilot signals and sequence pilot signal Construct a composite pilot injection path; The interleaved sampling timing deviation estimation module is used to obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled. Based on the composite pilot injection path, a multi-core correlation and frequency-assisted joint estimation mechanism is used to perform timing deviation extraction processing on the interleaved sampling signal sequence and output the timing deviation estimate value. The frequency response deviation function extraction module is used to perform delay compensation alignment and frequency domain distortion response extraction tasks on the interleaved sampled signal sequence based on the time-series deviation estimate, and outputs the frequency response deviation function. ; The frequency domain compensation module is used to calculate the frequency response deviation function. For each sub-channel in the interleaved sampled signal sequence The output signal is sequentially processed by frequency domain amplitude compensation and phase compensation, and the output channel is aligned with the corrected signal sequence. The SFDR-driven optimization control module is used to optimize each sub-channel in the interleaved sampled signal sequence based on the corrected signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the RF sampling reference signal sequence is finally output.

[0013] The present invention also provides a broadband radio frequency sampling device, comprising: a memory, a processor, and a broadband radio frequency sampling program stored in the memory and executable on the processor, wherein the broadband radio frequency sampling program implements a broadband radio frequency sampling method when executed by the processor.

[0014] The present invention also provides a computer program product, including a broadband radio frequency sampling program, which, when executed by a processor, implements the broadband radio frequency sampling method.

[0015] The beneficial effects of this invention are as follows: By introducing a composite pilot injection path (multi-tone minimum phase pilot and periodic m-sequence pilot), this invention can accurately extract the timing deviation of multi-interleaved ADCs under high frequency bandwidth and high sampling rate, and effectively compensate for frequency domain distortion, significantly improving signal quality and sampling accuracy under high dynamic range (SFDR ≥ 70dBc) conditions.

[0016] This invention, through dual-domain timing deviation estimation and SFDR feedback control mechanism, can complete the self-calibration of timing, gain, and bandwidth mismatch in real time under environments with temperature variations of ±40°C and power supply ripple interference, and the calibration convergence time does not exceed 10ms, meeting the stability and real-time requirements of 6G base stations and high-performance radio frequency systems. Attached Figure Description

[0017] To more clearly illustrate the technical solutions in the embodiments of the present invention or the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0018] Figure 1 This is a flowchart illustrating the first embodiment of a broadband radio frequency sampling method according to the present invention.

[0019] Figure 2 This is a schematic diagram of the multi-interleaved ADC structure and pilot injection of a first embodiment of a broadband radio frequency sampling method of the present invention.

[0020] Figure 3 This is a schematic diagram showing the comparison of the states before and after calibration in the first embodiment of a broadband radio frequency sampling method of the present invention.

[0021] Figure 4 This is a schematic diagram of a device for a broadband radio frequency sampling method according to the present invention. Detailed Implementation

[0022] The technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of the present invention, and not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0023] Example 1: As Figure 1 The diagram shown is a flowchart of the first embodiment of the broadband radio frequency sampling method of the present invention, which presents the first embodiment of the broadband radio frequency sampling method of the present invention.

[0024] In the first embodiment, the broadband radio frequency sampling method includes: Step S10: Acquire the multi-tone phase pilot signal at time t and sequence pilot signal Based on multi-tone phase pilot signals and sequence pilot signal Construct a composite pilot injection path; It should be noted that the composite pilot injection path, consisting of "multi-tone phase pilot signals" and "periodic m-sequence pilot signals," is used to efficiently estimate mismatch errors in multi-interleaved ADC structures. The multi-tone phase pilot signals provide extensive frequency domain information through pilot signals at multiple different frequency points, helping to identify gain mismatches and bandwidth mismatches in each channel. The periodic m-sequence pilot signals, on the other hand, provide independent calibration signals for each sub-channel in the time domain, helping to accurately capture timing deviations in each channel. These two types of pilot signals complement each other, ensuring sufficient compensation capability for errors in both the frequency and time domains.

[0025] Understandably, in multi-channel interleaved ADC structures (such as 16-channel TI-ADCs), due to the fixed phase sampling of each sub-channel at different times, clock skew and gain / bandwidth mismatch can lead to periodic image distortion spikes in the spectrum and phase misalignment of sampling points in different sub-channels, further causing waveform distortion during signal reconstruction. These errors are traditionally addressed by static calibration and external calibration signals; however, real-time monitoring and calibration are often impossible during operation. Therefore, this invention employs a composite pilot injection path to achieve real-time estimation and dynamic compensation of errors, thus avoiding the need for manual adjustment and recalibration required in traditional solutions.

[0026] It should be understood that this step, by introducing two types of low-power pilots into the multi-channel interleaved sampling structure, effectively solves the timing and frequency domain mismatch problem existing in high dynamic range and wideband signal sampling. Compared with the single pilot signal in traditional techniques, the composite pilot injection path can provide more information in both the time and frequency domains. Especially in complex RF signal environments, composite pilots can achieve higher precision calibration and broader error compensation.

[0027] For example, such as Figure 2The diagram illustrates the pilot injection and multi-channel interleaving composite structure employed in this embodiment of the invention: the main signal is superimposed with two types of low-power pilots: a multi-tone minimum phase pilot for accurately estimating amplitude and phase mismatch in the frequency domain, and a periodic m-sequence pilot for establishing a mapping of the response to each sub-channel in the time domain. Each sub-channel is sampled at uniform intervals, with colored dots representing multiple sub-ADC channels operating alternately; after all sub-ADC sampled data are aggregated, they enter the control modules such as the multiphase filter bank, fractional delay compensator, and digital equalizer. Step S20: Obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled, and perform time skew extraction processing on the interleaved sampling signal sequence using a multi-core correlation and frequency-assisted joint estimation mechanism based on the composite pilot injection path, and output the estimated time skew value. It should be noted that the "multi-core correlation and frequency-assisted joint estimation mechanism" is used to perform time skew extraction processing on interleaved sampled signal sequences based on composite pilot injection paths. Specifically, the multi-core correlation mechanism estimates the time alignment of the sampled signals of each sub-channel under the guidance of pilot signals at different frequencies; while the frequency-assisted estimation uses the frequency information of multi-tone phase pilot signals to optimize cross-band timing errors.

[0028] It should be understood that this step, by introducing a composite pilot injection path and a joint estimation mechanism, enables accurate estimation of timing skew under high dynamic range and high sampling rate conditions. Especially in multi-interleaved ADC structures, due to issues such as clock skew, gain mismatch, and bandwidth mismatch in the sampling of each sub-channel, traditional techniques typically can only perform calibration in a static environment and cannot cope with errors caused by real-time dynamic changes. In contrast, this invention, by combining multi-core correlation and frequency-assisted estimation, enables real-time online calibration, effectively eliminating timing errors in dynamic environments, thereby improving signal sampling accuracy and stability.

[0029] Step S30: Based on the time-series deviation estimate, perform delay compensation alignment and frequency domain distortion response extraction tasks on the interleaved sampled signal sequence, and output the frequency response deviation function. ; It should be noted that the timing deviation estimate is used to perform two tasks: delay compensation alignment and frequency domain distortion response extraction. The delay compensation alignment task uses fractional delay compensation to align the signal of each sub-channel in the time domain, thereby eliminating signal errors caused by timing deviations. The frequency domain distortion response extraction task analyzes the frequency domain differences between each sub-channel signal and the reference signal, extracts the frequency response deviation function, and quantizes the amplitude and phase mismatch. Ultimately, the results of these operations will contribute to subsequent signal calibration and distortion correction.

[0030] Understandably, this step generates a frequency response deviation function by compensating for the delay and extracting the frequency domain distortion response of each sub-channel in the interleaved sampled signal sequence. This function describes the amplitude and phase errors of each sub-channel relative to the reference channel. In a multi-interleaved ADC structure, each sub-channel is affected by timing deviations, gain mismatches, bandwidth differences, etc., when sampled at different time points, and therefore, these tasks must be used for precise correction.

[0031] It should be understood that this step addresses the multidimensional error problem in broadband signal sampling of multi-channel interleaved ADCs by performing corrections in both the frequency and time domains. Unlike traditional methods, which typically only correct for errors in the time or frequency domain separately, this invention combines time and frequency domain compensation to achieve efficient and accurate multidimensional mismatch compensation. Particularly in high-bandwidth and high-dynamic-range RF sampling, this dual calibration mechanism can significantly reduce spectral distortion and signal distortion, improving signal quality and dynamic range.

[0032] Step S40: Based on the frequency response deviation function For each sub-channel in the interleaved sampled signal sequence The output signal is sequentially processed by frequency domain amplitude compensation and phase compensation, and the output channel is aligned with the corrected signal sequence. It should be noted that, based on the frequency response deviation function output in step S30, frequency domain amplitude compensation and phase compensation are sequentially performed on the output signal of each sub-channel. Frequency domain amplitude compensation corrects the amplitude by constructing an appropriate compensation filter based on the amplitude difference component in the frequency response deviation function; phase compensation, on the other hand, adjusts the phase of the signal using a corresponding IIR all-pass filter structure by extracting the phase information from the frequency response deviation function, thereby eliminating errors caused by gain and phase mismatch. Finally, these compensated signal sequences are merged into a channel-aligned corrected signal sequence, providing an accurate input signal for subsequent signal reconstruction and high-precision processing.

[0033] Understandably, this step achieves channel alignment by performing frequency domain amplitude and phase compensation on the output signal of each sub-channel in the interleaved sampling signal sequence. Since frequency domain distortion often occurs in multi-channel interleaved sampling due to timing mismatch, gain difference, and bandwidth mismatch, this invention uses a frequency response deviation function combined with amplitude and phase compensation to accurately correct these mismatch problems in the frequency domain.

[0034] It should be understood that in a multi-channel interleaved ADC structure, the sampled signal of each sub-channel may be affected by various factors in the time and frequency domains, such as gain mismatch, bandwidth mismatch, and phase deviation. Traditional single amplitude compensation or phase compensation methods usually only solve one problem, resulting in incompletely accurate compensation results. However, this invention, through the combined processing of frequency domain amplitude compensation and phase compensation, can comprehensively eliminate these mismatches in the frequency domain, ensuring the relative consistency and accuracy of the signals of each sub-channel. In addition, the use of a frequency response deviation function for fine calculation makes the compensation process more accurate. Compared with traditional methods, it can effectively reduce signal distortion and sampling error, and improve dynamic range and signal-to-noise ratio.

[0035] Step S50: Based on the corrected signal sequence, process each sub-channel in the interleaved sampled signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the RF sampling reference signal sequence is finally output.

[0036] It's important to note that SFDR (Spurious-Free Dynamic Range) refers to the ratio between the dominant frequency component and the spurious components in the signal's spectrum. Spurious signals are typically caused by factors such as gain mismatch, timing deviations, and bandwidth mismatch. In wideband signal sampling systems, especially in multi-interleaved ADC structures, these problems often lead to significant spectral distortion. Spectral analysis transforms the signal from the time domain to the frequency domain by performing a Fourier transform, and then calculates the SFDR by matching the amplitude of the dominant frequency signal to the amplitude of the spurious signals. A low SFDR indicates the presence of strong spurious components in the signal, negatively impacting signal quality.

[0037] Understandably, this step involves performing spectral analysis on the signal of each sub-channel, calculating its SFDR value, and comparing it with a preset threshold. When the SFDR falls below the threshold, a dynamic amplitude injection and equalization feedback mechanism is automatically triggered to dynamically adjust the amplitude and frequency response of the sampled signal, thereby optimizing signal quality. This method can automatically adapt to external disturbances such as temperature changes and power supply noise in real-time operating environments, avoiding performance degradation caused by the inability to adjust in real time in traditional technologies. Compared to offline calibration in traditional technologies, this invention provides a real-time adaptive calibration scheme that effectively improves sampling accuracy and signal quality, and can operate stably under high dynamic range.

[0038] It should be understood that traditional multi-interleaved ADC structures typically rely on static external pilots or offline calibration techniques to compensate for time-domain and frequency-domain mismatches. However, these methods cannot cope with dynamic environmental changes in practical applications, such as temperature fluctuations and power supply interference. Under these changes, traditional techniques cannot quickly correct timing mismatches and frequency-domain distortions in the sampled signal, leading to a deterioration in signal quality. This invention, by combining a dynamic feedback mechanism of frequency-domain amplitude compensation and phase compensation, can compensate and optimize the signal in real time, ensuring synchronous calibration in the time and frequency domains, thereby improving the accuracy and reliability of the sampled signal.

[0039] For example, such as Figure 3 As shown, by simulating performance changes at different temperatures (-40°C to 80°C), the SFDR (Spurious Dynamic Range) curves before and after calibration were plotted. Before calibration, the SFDR decreased rapidly with increasing temperature, from approximately 65 dBc at 25°C to less than 58 dBc at the extreme temperature, exhibiting obvious thermal drift mismatch characteristics. After calibration, the SFDR stabilized at around 70 dBc with a small fluctuation range, indicating that the calibration mechanism effectively suppressed the spectral image distortion caused by timing mismatch and gain changes, meeting the link requirements of high linearity and low intermodulation in 6G base station systems. Compared with traditional single-temperature calibration schemes, which cannot correct ADC interleaving errors under dynamic environmental changes, this scheme demonstrates advantages such as minimal temperature influence, short convergence time, and dynamic recoverability.

[0040] Example 2: Furthermore, the present invention provides a broadband radio frequency sampling device that employs a broadband radio frequency sampling method as described in the above embodiments, thereby solving a technical problem related to broadband radio frequency sampling. Compared with the prior art, the beneficial effects of the broadband radio frequency sampling device provided by the present invention are the same as those of the broadband radio frequency sampling method provided in the above embodiments, and other technical features of the broadband radio frequency sampling device are the same as those disclosed in the methods of the above embodiments, and will not be repeated here.

[0041] Example 3: This invention provides a broadband radio frequency sampling device, please refer to... Figure 4A broadband radio frequency (RF) sampling device includes: at least one processor; and a memory communicatively connected to the at least one processor; wherein the memory stores instructions executable by the at least one processor, which, when executed by the at least one processor, enable the at least one processor to perform a broadband RF sampling method as described in Embodiment 1 above. The broadband RF sampling device in this embodiment may include, but is not limited to, mobile terminals such as mobile phones, laptops, digital broadcast receivers, PDAs (Personal Digital Assistants), PADs (Portable Application Description), PMPs (Portable Media Players), and in-vehicle terminals (e.g., in-vehicle navigation terminals), as well as fixed terminals such as digital TVs and desktop computers. This broadband RF sampling device is merely an example and should not impose any limitations on the functionality and scope of use of the embodiments of this invention. A broadband RF sampling device may include a processing device 1001 (e.g., a central processing unit, a graphics processing unit, etc.), which can perform various appropriate actions and processes according to a program stored in a read-only memory 1002 or a program loaded from a storage device 1003 into a random access memory 1004. The random access memory 1004 also stores various programs and data required for the operation of the broadband RF sampling device. Processing device 1001, read-only memory 1002, and random access memory 1004 are interconnected via bus 1005. I / O interface 1006 is also connected to the bus. Typically, the following devices can be connected to I / O interface 1006: input devices 1007 including, for example, touch screens, touchpads, keyboards, mice, image sensors, microphones, accelerometers, gyroscopes, etc.; output devices 1008 including, for example, liquid crystal displays (LCDs), speakers, vibrators, etc.; storage devices 1003 including, for example, magnetic tapes, hard disks, etc.; and communication devices 1009. Communication device 1009 allows a broadband RF sampling device to communicate wirelessly or wiredly with other devices to exchange data. Although a broadband RF sampling device with various devices is shown in the figure, it should be understood that it is not required to implement or have all the devices shown. More or fewer devices may be implemented or have alternatively.

[0042] Example 4: This invention also provides a computer program product, including a computer program that, when executed by a processor, implements the steps of the broadband radio frequency sampling method described above. The computer program product provided by this invention can solve a technical problem related to broadband radio frequency sampling. Compared with the prior art, the beneficial effects of the computer program product provided by this invention are the same as those of the broadband radio frequency sampling method provided in the above embodiments, and will not be repeated here.

[0043] In particular, according to the embodiments disclosed in this invention, the processes described above with reference to the flowcharts can be implemented as computer software programs. For example, embodiments of this invention include a computer program product comprising a computer program carried on a computer-readable medium, the computer program containing program code for performing the methods shown in the flowcharts. In such embodiments, the computer program can be downloaded and installed from a network via a communication device, or installed from storage device 1003, or installed from read-only memory 1002. When the computer program is executed by processing device 1001, it performs the functions defined in the methods of the embodiments disclosed in this invention.

[0044] It should be understood that the various parts disclosed in this invention can be implemented using hardware, software, firmware, or a combination thereof. In the description of the above embodiments, specific features, structures, materials, or characteristics may be combined in any suitable manner in one or more embodiments or examples.

[0045] Obviously, those skilled in the art can make various modifications and variations to this invention without departing from its spirit and scope. Therefore, if these modifications and variations fall within the scope of the claims of this invention and their equivalents, this invention also intends to include these modifications and variations.

Claims

1. A broadband radio frequency sampling method, characterized in that, The methods include: Step S10: Acquire the multi-tone phase pilot signal at time t and sequence pilot signal Based on multi-tone phase pilot signals and sequence pilot signal Construct a composite pilot injection path; Step S20: Obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled, and perform timing deviation extraction processing on the interleaved sampling signal sequence using a multi-core correlation and frequency-assisted joint estimation mechanism based on the composite pilot injection path, and output the timing deviation estimate. Step S30: Based on the time-series deviation estimate, perform delay compensation alignment and frequency domain distortion response extraction tasks on the interleaved sampled signal sequence, and output the frequency response deviation function. ; Step S40: Based on the frequency response deviation function For each sub-channel in the interleaved sampled signal sequence The output signal is sequentially processed by frequency domain amplitude compensation and phase compensation, and the output channel is aligned with the corrected signal sequence. Step S50: Based on the corrected signal sequence, process each sub-channel in the interleaved sampled signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the RF sampling reference signal sequence is finally output.

2. The broadband radio frequency sampling method as described in claim 1, characterized in that, In step S10, the multi-tone phase pilot signal ,in, This represents the amplitude of the k-th pilot frequency; This is the frequency of the k-th pilot signal; This is the phase of the k-th pilot. The number of pilot frequencies.

3. The broadband radio frequency sampling method as described in claim 1, characterized in that, Step S20 involves obtaining the interleaved sampling signal sequence output from the multi-channel interleaved ADC structure to be sampled, and performing timing deviation extraction processing on the interleaved sampling signal sequence using a multi-core correlation and frequency-assisted joint estimation mechanism based on the composite pilot injection path, and outputting the timing deviation estimate. Specifically, this includes: Step S201: Obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled. For each sub-channel in the interleaved sampling signal sequence... output signal Output signal of the preset reference channel The sliding cross-correlation calculation is performed using a sliding method with a windowed function to obtain the results for each sub-channel. Sliding cross-correlation score sequence Based on sliding cross-correlation score sequence The output time-domain estimate of the time corresponding to the peak position in the middle. Where n is the index of the sampling point; Step S202: Based on the multi-tone phase pilot signal The k-th pilot frequency is calculated using a differential phase extraction method based on spectrum analysis. The phase difference value is calculated, and a least-squares fitting method is used to perform linear slope fitting on the phase difference value, and the output is compared with the sub-channel. The corresponding frequency domain estimate ; Step S203: Based on time domain estimates and frequency domain estimates The timing bias estimate is calculated using a dynamic weighted fusion mechanism, and the sub-channel is output. Final time series bias estimate .

4. The broadband radio frequency sampling method as described in claim 3, characterized in that, In step S201, the sliding cross-correlation score sequence ,in, The length of the sliding window; This is the delay offset of the sliding cross-correlation; This indicates that the reference channel output signal is delayed in the time domain. Signal sample values ​​after each sampling point; The window function is a preset window function, including Hamming window, Kaiser window or cosine window, used to suppress edge effects with weights.

5. The broadband radio frequency sampling method as described in claim 1, characterized in that, In step S30, delay compensation alignment and frequency domain distortion response extraction are performed on the interleaved sampled signal sequence based on the time-series deviation estimate, and the frequency response deviation function is output. The steps specifically include: Step S301: First, perform a delay compensation alignment task on the interleaved sampled signal sequence based on the timing deviation estimate, utilizing each sub-channel. Corresponding time series deviation estimate Construct a compensation filter bank; Step S302: Then, based on the compensation filter bank, process each sub-channel in the interleaved sampled signal sequence. output signal Perform digital delay compensation and output aligned signal ; Step S303: Finally, for the aligned signals Perform a Discrete Fourier Transform (DFT) and, in conjunction with the frequency domain response of the reference channel corresponding to the preset reference channel output signal, extract each sub-channel. Frequency response deviation function .

6. The broadband radio frequency sampling method as described in claim 1, characterized in that, In step S40, the frequency domain amplitude compensation processing specifically includes: constructing a digital gain equalizer based on a preset amplitude deviation function, and correcting each sub-channel based on the digital gain equalizer. The amplitude response error of the output signal; frequency domain phase compensation processing specifically includes: constructing a phase equalization network based on an IIR filter based on a preset phase deviation function, and correcting and aligning each sub-channel based on the phase equalization network. The phase response of the output signal.

7. The broadband radio frequency sampling method as described in claim 1, characterized in that, In step S50, each sub-channel in the interleaved sampling signal sequence is processed based on the corrected signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the final output of the RF sampling reference signal sequence includes the following steps: Step S501: Based on the corrected signal sequence, process each sub-channel in the interleaved sampled signal sequence. The signal spectrum was calculated using the high-resolution spectral estimation method ESPRIT; the positions of the target dominant frequency component and non-dominant frequency components in the signal spectrum were identified, and the main lobe power corresponding to the target dominant frequency component position was obtained. Stray power corresponding to non-dominant frequency component positions Based on main lobe power Stray power corresponding to non-dominant frequency component positions Calculate each sub-channel Corresponding spurious-free dynamic range index , It also outputs a set of SFDR indicators; Step S502: Pre-set the indicator threshold value γ; when there is no spurious dynamic range indicator When the value is less than the preset threshold γ, the channel alignment correction signal sequence is determined to be invalid, and a dynamic amplitude injection and equalization feedback mechanism is triggered. The dynamic amplitude injection and equalization feedback mechanism specifically includes: Dynamic amplitude injection: superimposing a preset set of low-amplitude frequency domain pilot signals onto the sub-channel. Equalization feedback mechanism: After dynamic amplitude injection is completed, the frequency response deviation function is updated; when there is no spurious dynamic range index When the value is greater than or equal to the preset index threshold value γ, the channel alignment correction signal sequence is determined to be valid, and the process proceeds to step S503. Step S503: For channels whose channel alignment correction signal sequence is valid, the correction signal sequence is output as the RF sampling reference signal sequence; for channels that trigger dynamic amplitude injection and equalization feedback mechanisms, the output signal is subjected to secondary correction processing according to the updated frequency response deviation function, including sequentially performing frequency domain amplitude compensation processing and phase compensation processing, and finally outputting the RF sampling reference signal sequence.

8. A broadband radio frequency sampling device, applied to the broadband radio frequency sampling method according to any one of claims 1 to 7, characterized in that, The broadband radio frequency sampling device includes: The pilot injection path construction module is used to acquire the multi-tone phase pilot signal at time t. and sequence pilot signal Based on multi-tone phase pilot signals and sequence pilot signal Construct a composite pilot injection path; The interleaved sampling timing deviation estimation module is used to obtain the interleaved sampling signal sequence output by the multi-channel interleaved ADC structure to be sampled. Based on the composite pilot injection path, a multi-core correlation and frequency-assisted joint estimation mechanism is used to extract the timing deviation of the interleaved sampling signal sequence and output the timing deviation estimate. The frequency response deviation function extraction module is used to perform delay compensation alignment and frequency domain distortion response extraction tasks on the interleaved sampled signal sequence based on the time-series deviation estimate, and outputs the frequency response deviation function. ; The frequency domain compensation module is used to calculate the frequency response deviation function. For each sub-channel in the interleaved sampled signal sequence The output signal is sequentially processed by frequency domain amplitude compensation and phase compensation, and the output channel is aligned with the corrected signal sequence. The SFDR-driven optimization control module is used to optimize each sub-channel in the interleaved sampled signal sequence based on the corrected signal sequence. The spurious-free dynamic range index was calculated using the spectrum analysis method. When there is no spurious dynamic range index When the value is less than the preset threshold γ, the dynamic amplitude injection and equalization feedback mechanism is triggered, and the RF sampling reference signal sequence is finally output.

9. A broadband radio frequency sampling device, characterized in that, The broadband radio frequency sampling device includes: a memory, a processor, and a broadband radio frequency sampling program stored in the memory and executable on the processor. When the broadband radio frequency sampling program is executed by the processor, it implements a broadband radio frequency sampling method according to any one of claims 1 to 7.

10. A computer program product, characterized in that, The computer program product includes a broadband radio frequency sampling program, which, when executed by a processor, implements a broadband radio frequency sampling method according to any one of claims 1 to 7.

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