A linear polarized in-band co-polarized scattering reconfigurable array antenna

Abstract

The application relates to a linearly polarized in-band co-polarized scattering reconfigurable array antenna, which comprises an antenna module arranged in an array by a plurality of same antenna units. Each antenna unit adopts a multi-layer stacked structure: from top to bottom, a radiation patch, a first dielectric substrate, a metal patch, a second dielectric substrate, a metal ground plate and a third dielectric substrate are sequentially arranged. A plurality of metalized through holes are arranged on the center line of the first dielectric substrate, and the metalized through holes, the metal patch and the metal ground plate jointly form a resonator. Each unit is also integrated with a reflective phase shifter, which comprises a microstrip transmission line, a feeding metal column, a metal short circuit column and a varactor diode. The feeding metal column penetrates through the layers and is connected with the radiation patch, and the metal short circuit column is connected with the metal ground plate. The varactor diode receives external control through a direct current bias line, the reflection phase of the unit is adjusted by changing the bias voltage, and the in-band co-polarized scattering reconfigurable function of the antenna is realized. The device can realize flexible regulation and control of a wide range and low coupling of scattering characteristics while maintaining high stable radiation characteristics.

Description

Technical Field

[0001] This invention belongs to the fields of antenna technology and microwave engineering technology, and specifically relates to a linearly polarized in-band co-polarized scattering reconfigurable array antenna. Background Technology

[0002] Antennas are core components in wireless communication and detection systems. Within their operating frequency band, they generate significant electromagnetic scattering, contributing a large radar cross section and posing challenges to the overall electromagnetic compatibility and low detectability of the system. To suppress in-band scattering, researchers have developed various methods, including structural modification, coating with absorbing materials, and employing metamaterial structures.

[0003] On the other hand, with the increasing complexity of electromagnetic application environments, the requirements for the dynamic adaptability of antenna performance are constantly increasing. Traditional scattering control methods based on fixed structures have limited control capabilities and are difficult to respond to changing external conditions in real time. Therefore, antenna technology with dynamic scattering reconstruction capabilities has attracted widespread attention.

[0004] As a special type of scatterer, an antenna's scattered field can be divided into structure-related mode terms and antenna mode terms related to load mismatch re-radiation. This means that when performing co-polarization scattering modulation within the antenna's operating frequency band, the radiation and scattering paths overlap. Without coordinated design, the modulation of scattering performance can easily interfere with the antenna's normal radiation function.

[0005] Currently, antenna design for linearly polarized and in-band co-polarized scattering still faces many challenges, including: complex structural design, low radiation efficiency, limited achievable scattering states, and most importantly, significant coupling between radiation and scattering performance, which is difficult to control independently. This severely restricts the performance and integration of antennas.

[0006] In summary, the main problem with existing technologies lies in how to achieve flexible, wide-range, dynamic, and low-coupling control of the antenna's scattering characteristics while maintaining high stability of its radiation characteristics. Summary of the Invention

[0007] To address the aforementioned problems in the prior art, this invention provides a linearly polarized in-band co-polarized scattering reconfigurable array antenna. The technical problem to be solved by this invention is achieved through the following technical solution:

[0008] This invention provides a linearly polarized in-band co-polarized scattering reconfigurable array antenna, comprising: an antenna module, the antenna module including... Multiple antenna elements with the same structure arranged in an array form. and All are positive integers;

[0009] Each antenna element includes:

[0010] The following components are stacked sequentially from top to bottom in the z-direction: a radiating patch, a first dielectric substrate, a metal patch, a second dielectric substrate, a metal ground plane, and a third dielectric substrate.

[0011] Along the x-direction, a plurality of metallized vias are equally spaced at the center line of the first dielectric substrate for contacting the metal patch, thereby forming a resonator structure together with the metal patch and the metal ground plane.

[0012] Each antenna element further includes: a reflective phase shifter; the reflective phase shifter includes a microstrip transmission line, and a feed metal post, a metal short-circuit post, and a varactor diode disposed on the microstrip transmission line;

[0013] The feeding metal post passes through the first through hole and contacts the radiating patch. The first through hole sequentially passes through the third dielectric substrate, the metal ground plane, the second dielectric substrate, the first dielectric substrate, and the radiating patch. The metal short-circuit post passes through the second through hole and contacts the metal ground plane. The second through hole passes through the third dielectric substrate. The varactor diode is connected to an external control unit via a DC bias line to change its DC bias voltage in response to a control signal sent by the external control unit, thereby changing the reflection phase of the scattered field of each antenna element and realizing the reconfigurable scattering function of the antenna.

[0014] Compared with the prior art, the beneficial effects of the present invention include:

[0015] 1. Achieved efficient decoupling and independent control of radiation and scattering performance: This scheme separates radiation and scattering control performance through a multi-layer resonator structure, providing a stable benchmark for the antenna's radiation characteristics (such as impedance matching and radiation pattern). The good consistency between antenna elements and the integrated feeding method ensure that the array maintains stable and efficient radiation performance under various scattering conditions. Furthermore, the reflection phase of each element can be precisely controlled by changing the DC bias voltage of the varactor diode on the reflective phase shifter, thus achieving flexible reconstruction of the scattered wavefront without interfering with the antenna's normal radiation function. This effectively solves the core problem of the mutual constraint between scattering control and radiation performance in traditional designs.

[0016] 2. Compact structure and high integration: The antenna adopts a multi-layer stacked integrated design, vertically integrating the through-hole SMP connector, resonator structure, and reflective phase shifter. This three-dimensional integration method greatly improves space utilization and avoids the complex feeding structure and additional space occupation caused by traditional external phase shifting networks, making the antenna system structure simpler and more compact.

[0017] 3. Flexible and diverse scattering control: Based on the electrical tuning method of semiconductor devices, the equivalent scattering field distribution of the entire array can be rapidly and continuously changed within milliseconds by controlling the bias voltage of each unit through programming. This enables the antenna to dynamically generate multiple scattering modes (such as beam deflection, scattering diffusion, etc.), realizing a leap from "single fixed" to "multi-state reconfigurable", and has stronger environmental adaptability. Attached Figure Description

[0018] Figure 1 This is a schematic diagram of the structure of a linearly polarized in-band co-polarized scattering reconfigurable array antenna provided in an embodiment of the present invention;

[0019] Figure 2 This is a schematic diagram of the antenna unit provided in an embodiment of the present invention;

[0020] Figure 3 This is a schematic diagram showing the location of the metallized vias in the first dielectric substrate provided in an embodiment of the present invention;

[0021] Figure 4 This is a schematic diagram of the position of the reflective phase shifter provided in an embodiment of the present invention;

[0022] Figure 5 This is a diagram showing the routing design and partial enlargement of the DC bias line provided in an embodiment of the present invention.

[0023] Figure 6 This is a simulation diagram of the varactor diode following the control signal sent by the FPGA, provided in an embodiment of the present invention.

[0024] Figure 7 These are characterization diagrams of a single antenna element under radiative excitation provided in the embodiments of the present invention, wherein (a) is a simulation diagram of the surface current distribution under radiative excitation of a single antenna element, and (b) is a radiation pattern under radiative excitation of a single antenna element;

[0025] Figure 8 This is a system simulation diagram of the antenna element following the change of the varactor diode provided in the embodiment of the present invention; wherein, (a) is S 11 (a) Simulation diagram of parameters following the varactor diode; (b) Simulation diagram of peak gain of scattered field following the varactor diode; (c) Simulation diagram of radiation characteristics of scattered field following the varactor diode.

[0026] Figure 9 The diagram shows the result of the antenna element reflection characteristics changing with capacitance according to the embodiment of the present invention; wherein, (a) is a schematic diagram of the amplitude change of vertically incident co-polarized reflection, and (b) is a schematic diagram of the phase change of vertically incident co-polarized reflection.

[0027] Figure 10These are simulation results of the scattering reduction performance of the linearly polarized in-band co-polarized scattering reconfigurable array antenna provided in this embodiment of the invention at a frequency of 9 GHz and under the condition of phi-polarized vertical incidence.

[0028] Figure 11 This is a simulation diagram of the active beam control capability of the linearly polarized in-band co-polarized scattering reconfigurable array antenna provided in this embodiment of the invention at a frequency of 9 GHz and under the condition of phi-polarized vertical incidence.

[0029] Figure 12 This is a simulation result of the radiation gain pattern of the linearly polarized band co-polarized scattering reconfigurable array antenna at 9 GHz frequency and in the yoz plane (E plane) provided in this embodiment of the invention.

[0030] Explanation of icon numbers:

[0031] 1-Antenna element; 2-DC bias line; 3-First pin header; 4-Second pin header; 5-Inductor; 6-Plastic screw and nut;

[0032] 11-Radiating patch; 12-First dielectric substrate; 13-Metal patch; 14-Second dielectric substrate; 15-Metal ground plane; 16-Third dielectric substrate; 17-Reflective phase shifter; 18-Through-hole SMP connector;

[0033] 121 - Metallized via; 171 - Microstrip transmission line; 172 - Feed metal post; 173 - Metal shorting post; 174 - Varactor diode; 181 - Feed port;

[0034] 1711 - First microstrip line; 1712 - Second microstrip line; 1713 - Third microstrip line; 1731 - First short-circuit post; 1732 - Second short-circuit post; 1741 - First varactor diode; 1742 - Second varactor diode. Detailed Implementation

[0035] The present invention will be further described in detail below with reference to specific embodiments, but the implementation of the present invention is not limited thereto.

[0036] In the description of this invention, the terms "first" and "second" are used for descriptive purposes only and should not be construed as indicating or implying relative importance or implicitly specifying the number of indicated technical features. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more of that feature. In the description of this invention, "a plurality of" means two or more, unless otherwise explicitly specified.

[0037] Although the invention has been described herein in conjunction with various embodiments, those skilled in the art will understand and implement other variations of the disclosed embodiments by reviewing the accompanying drawings, disclosure, and appended claims in carrying out the claimed invention. In the claims, the word "comprising" does not exclude other components or steps, and "a" or "an" does not exclude a plurality. A single processor or other unit can implement several functions listed in the claims. While different dependent claims may recite certain measures, this does not mean that these measures cannot be combined to produce good results.

[0038] The present invention will now be described in detail with reference to the accompanying drawings, providing a reconfigurable array antenna for in-band linear polarization scattering.

[0039] Figure 1 This is a schematic diagram of the structure of a linearly polarized band co-polarized scattering reconfigurable array antenna provided in an embodiment of the present invention. Figure 2 This is a schematic diagram of the antenna unit provided in an embodiment of the present invention. Figure 1-2 As shown, the linearly polarized band co-polarized scattering reconfigurable array antenna includes: an antenna module, the antenna module comprising: Multiple antenna elements 1 with identical structures arranged in an array form, and All are positive integers; each antenna element 1 includes: a radiating patch 11, a first dielectric substrate 12, a metal patch 13, a second dielectric substrate 14, a metal ground plane 15, and a third dielectric substrate 16 stacked sequentially from top to bottom in the z-direction; wherein, along the x-direction, a plurality of metallized vias 121 are equally spaced at the center line of the first dielectric substrate 12 for contacting the metal patch 13, thereby forming a resonator structure together with the metal patch 13 and the metal ground plane 15; each antenna element 1 also includes: a reflective phase shifter 17; the reflective phase shifter 17 includes a microstrip transmission line 171, and a feed metal post 172 disposed on the microstrip transmission line 171, and a metal short The antenna includes a post 173, a varactor diode 174, and a feed metal post 172 that passes through a first through hole and contacts the radiating patch 11. The first through hole sequentially passes through the third dielectric substrate 16, the metal ground plane 15, the second dielectric substrate 14, the first dielectric substrate 12, and the radiating patch 11. The metal short-circuit post 173 passes through a second through hole and contacts the metal ground plane 15. The second through hole passes through the third dielectric substrate 16. The varactor diode 174 is connected to an external control unit via a DC bias line 2 to change its DC bias voltage in response to a control signal sent by the external control unit, thereby changing the reflection phase of the scattered field of each antenna element 1 and realizing the reconfigurable scattering function of the antenna.

[0040] For example, the external control unit is a field-programmable gate array (FPGA).

[0041] Please refer to Figure 2 Each antenna element 1 further includes: a through-hole SMP connector 18; the through-hole SMP connector 18 and the reflective phase shifter 17 are symmetrically arranged in the y-direction; the probe of the through-hole SMP connector 18 passes through a third through-hole and contacts the radiating patch 11, wherein the third through-hole sequentially passes through the third dielectric substrate 16, the metal ground plane 15, the second dielectric substrate 14, the metal patch 13, the first dielectric substrate 12, and the radiating patch 11. The through-hole SMP connector 18 is a miniature, blind-mating, push-in RF coaxial connector, model SMP-JHD5. It can complete the connection and locking through axial pushing force, providing a reliable RF connection in a limited space. The operating frequency range of the through-hole SMP connector 18 can vary from DC (0Hz) to 40GHz.

[0042] In other words, the radiating patch 11 is a two-port type, and the metallized via 121, the metal patch 13 and the metal ground plane 15 together form a resonator structure, the purpose of which is to achieve high isolation characteristics between the two ports of the radiating patch 11.

[0043] Here, the through-hole SMP connector 18 is soldered to the bottom of the third dielectric substrate 16 and is connected to one port (i.e., the third through hole) of the radiating patch 11 through its probe. The reflective phase shifter 17 is also fixed to the bottom of the third dielectric substrate 16 and is in contact with the other port (i.e., the first through hole) of the radiating patch 11 through its power supply metal post 172.

[0044] Please continue to refer to Figure 2 Along the y-direction, the width of the metal patch 13 The distance is less than that between the through-hole SMP connector 18 and the reflective phase shifter 17. Here, the upper and lower surfaces of the second dielectric substrate 14 are unetched and are bare boards, the purpose of which is to create a gap between the metal patch 13 and the perforated metal ground plane 15 to obtain a capacitive effect.

[0045] Figure 3 This is a schematic diagram showing the location of the metallized via 121 in the first dielectric substrate 12 provided in this embodiment of the invention. Please refer to... Figure 2 and Figure 3 For example, each antenna element 1 is a cube with a side length of 15mm, and the spacing between two adjacent antenna elements 1 is 15mm. The radiating patch 11 and the metal patch 13 in each antenna element 1 are both rectangular sheet structures. The length of the radiating patch 11... =7.625mm, width =7.75mm, the distance between the two ports (the first through hole and the third through hole) of the radiating patch 11 The diameter is 7.1mm, and the diameter of each port is 0.05mm. Therefore, the distance between the power supply metal post 172 and the probe of the through-hole SMP connector 18 is... The diameter is 6.62 mm. Here, the diameter of the feed metal post 172 is 0.38 mm. The width of the metal patch 13... =1.4mm, length =8.25mm, the thickness of the first dielectric substrate 12 =1.982mm. Furthermore, the number of metallized vias 121 is 11, and the diameter of each metallized via 121 is... The spacing between adjacent metallized vias 121 is 0.4 mm. The thickness is 0.7 mm. The thickness of the second dielectric substrate 14 is... The thickness of the third dielectric substrate 16 is 0.127 mm. It is 0.5mm.

[0046] Here, the first dielectric substrate 12 and the second dielectric substrate 14 are made of F4B with a relative permittivity of 2.65 and a loss tangent of 0.002, and the third dielectric substrate 16 is made of Rogers RO3006 with a relative permittivity of 6.15 and a loss tangent of 0.0025.

[0047] Figure 4 This is a schematic diagram showing the position of the reflective phase shifter 17 provided in an embodiment of the present invention. Please refer to... Figure 2-4 As shown, the microstrip transmission line 171 includes a first microstrip line 1711, a second microstrip line 1712, and a third microstrip line 1713, which form an "L" shape. The varactor diode 174 includes a first varactor diode 1741 and a second varactor diode 1742. The metal short-circuit post 173 includes a first short-circuit post 1731 and a second short-circuit post 1732. Along the x-direction, the first connection end of the first microstrip line 1711 is provided with a feeding metal post 172. A second terminal of microstrip line 1711 is connected to the cathode of a first varactor diode 1741, and the anode of the first varactor diode 1741 is connected to one end of a second microstrip line 1712. The other end of the second microstrip line 1712 has a first short-circuit post 1731. Along the y-direction, a third terminal of the first microstrip line 1711 is connected to the cathode of the second varactor diode 1742, and the anode of the second varactor diode 1742 is connected to one end of a third microstrip line 1713. The other end of the third microstrip line 1713 has a second short-circuit post 1732. It should be noted that the first varactor diode 1741 and the second varactor diode 1742 change synchronously.

[0048] For example, the first varactor diode 1741 and the second varactor diode 1742 are model MA46H120. The overall length along the x-direction is... The width is 5.4 mm; the width of the first microstrip line 1711 is... The distance is 0.5 mm; the distance from the third microstrip line 1713 along the x-direction to the first short-circuit post 1731. The overall length of the second varactor diode 1742 and the third microstrip line 1713 is 4.4 mm along the y-direction. The diameter is 1mm. Among them, the diameter of the metal short-circuit post 173 is 0.5mm.

[0049] It should be noted that, in Figure 4 In the middle, the hole on one side of the reflective phase shifter 17 is the bottom power supply port 181 of the through-hole SMP connector 18.

[0050] Please continue to refer to Figure 1 In one possible implementation, and The values ​​are all 8. That is, this linearly polarized band co-polarized scattering reconfigurable array antenna includes 8×8 antenna elements 1; and the antenna module also includes... Threaded holes arranged in an array, and All are positive integers; along the x or y direction, each column of threaded holes is located between two adjacent columns of antenna elements 1 for threaded connection with plastic screws and nuts 6. Here, and All are 5. Here, each antenna element 1 can independently adjust the reflection phase of its own scattered field. Specifically, the range of the reflection phase of the scattered field of each antenna element 1 is 0°~300°.

[0051] Figure 5 This is a partial enlarged view of the routing design of the DC bias line provided in an embodiment of the present invention. It should be noted that the partial enlarged view shows the connection method of the DC bias line 2 to the pin header and the antenna element 1, respectively.

[0052] like Figure 5As shown, the linearly polarized band in-band co-polarized scattering reconfigurable array antenna also includes: a first group of pin headers 3 and a second group of pin headers 4 with identical structures; the first group of pin headers 3 and the second group of pin headers 4 are respectively arranged on two symmetrical sides of the antenna module along the x-direction; multiple groups of DC bias lines 2 are connected between the first group of pin headers 3 and the second group of pin headers 4 to connect to an external control unit through the first group of pin headers 3 and the second group of pin headers 4; each group of DC bias lines 2 is connected to multiple antenna elements 1 through multiple inductors 5, with one inductor 5 corresponding to one antenna element 1.

[0053] For example, each pin header includes four sets of probes. An inductor 5 is applied between the DC bias line 2 and the reflective phase shifter 17 to isolate the radio frequency signal, and the DC bias line 2 is led to both ends by the routing design. Here, the two sets of pin headers pass through and are fixed to the entire antenna board, connected to the external control unit, receiving DC power from the external control unit, and sending control signals to the antenna unit 1.

[0054] The above is a structural description of the linearly polarized band co-polarized scattering reconfigurable array antenna provided in the embodiments of the present invention.

[0055] The linearly polarized in-band co-polarized scattering reconfigurable array antenna provided in this embodiment of the invention is now tested using the simulation software ANSYS HFSS.

[0056] Figure 6 This is a simulation diagram of a varactor diode following the control signal sent by an FPGA, as provided in an embodiment of the present invention. Here, the control signal sent by the FPGA is a voltage signal. Figure 7 This is a surface current distribution and radiation pattern of a single antenna element under radiative excitation, provided in an embodiment of the present invention. Figure 7 (a) in the figure is a simulation diagram of the surface current distribution when the antenna element is radiated. Figure 7 (b) in the diagram shows the radiation pattern of the scattered field when the antenna element is radiated. For example... Figure 7 As shown in (a), the current is mainly distributed on the left radiating patch, which also verifies the isolation characteristics of antenna element 1. Figure 7 As shown in (b), due to the asymmetric nature of the actual radiating patch, the peak gain of the gain pattern is not in the normal direction but is deflected to 30°.

[0057] Figure 8 This is a system simulation diagram illustrating how the antenna element follows the changes of the varactor diode, as provided in an embodiment of the present invention. Figure 8 (a) in the text is S 11 Simulation graph showing how the parameter (reflection coefficient) changes with the varactor diode. Figure 8 (b) in the figure is a simulation diagram showing the peak gain of the scattered field following the variation of the varactor diode. Figure 8(c) in the figure is a simulation diagram showing the radiation characteristics of the scattered field following the change of the varactor diode. For example... Figure 8 As shown in (a), all curves maintain good depth and shape within the operating frequency band from 8.9 GHz to 9.1 GHz, indicating that the impedance matching performance of the antenna is not sensitive to capacitance changes within this frequency band and the operating frequency band is stable. Figure 8 Figure (b) directly depicts the peak gain of the antenna as a function of capacitance at the 9 GHz frequency. The curve clearly shows that the antenna gain fluctuation is very small throughout the entire capacitance variation range, with a variation amplitude of less than 1 dB, which ensures the stability of the antenna radiation intensity. Figure 8 Figure (c) shows the curve of the antenna's radiated phase as a function of capacitance. As shown, the phase change is controlled within 20°. This small change indicates that capacitor tuning has minimal impact on the antenna's radiated phase, which is beneficial for maintaining the stability of characteristics such as beam pointing. Combining the three sub-figures, it can be seen that this antenna design, through capacitor tuning, successfully achieves high stability of radiation characteristics (including impedance, gain, and phase) in the frequency band near its center frequency of 9 GHz, meeting the requirements of application scenarios with high performance consistency requirements.

[0058] Figure 9 This is a graph showing the result of the antenna element reflection characteristics changing with capacitance, provided in an embodiment of the present invention. Figure 9 (a) in the diagram is a schematic diagram showing the amplitude variation of vertically incident co-polarized reflection. Figure 9 (b) in the diagram is a schematic diagram of the phase change of vertically incident co-polarized reflection. Figure 9 Figure (a) shows the return loss curves for different capacitance values ​​(from C=0.15pF to C=1.40pF) in the 8.0GHz to 10.0GHz frequency band. The vertical axis represents the reflection amplitude (dB), with a lower value indicating better antenna impedance matching and less energy reflection. It can be observed that despite the change in capacitance, all curves maintain a relatively smooth trend throughout the frequency band, with fluctuations controlled within 5dB. This amplitude stability is attributed to the combined effect of antenna mode terms and antenna structure mode terms in the antenna design, ensuring good matching performance during tuning. Figure 9In Figure (b), the vertical axis represents the reflection phase (unit: deg, degrees (°)). The phase curves corresponding to different capacitance values ​​are clearly distributed in the figure. The most significant feature is that the reflection phase exhibits a tuning range of up to approximately 300° within the indicated frequency band. This means that by changing the capacitance value, the reflection phase response of antenna element 1 can be effectively and over a wide range. In other words, the antenna element 1 provided by this invention, through capacitor tuning, can achieve a wide range of adjustment of the reflection phase exceeding 300° while maintaining a relatively stable reflection amplitude (change <5dB). This characteristic makes the antenna element 1 very suitable as a core component in advanced antenna systems (such as phased arrays, reconfigurable smart surfaces, etc.) that require phase scanning or beamforming, because the phase state of each antenna element 1 can be precisely controlled by capacitance.

[0059] Figure 10 This is the simulation result of the scattering reduction performance of the linearly polarized in-band co-polarized scattering reconfigurable array antenna provided in this embodiment of the invention at a frequency of 9 GHz and under the condition of phi-polarized vertical incidence. Figure 10 As shown, by optimizing the DC bias voltage fed to each antenna element (thereby precisely controlling the capacitance value of the varactor diode 174 inside each antenna element 1), the scattering mode modulation capability of the array was successfully activated. It can be clearly seen from the figure that the optimized radiation characteristics have changed significantly: (1) near 0 degrees (i.e., monostatic direction), the RCS value represented by the red dashed line is significantly lower than that of the black solid line; (2) at a 9 GHz operating frequency and under vertical incidence (0 degrees) conditions, the monostatic RCS of the antenna provided by this invention is effectively reduced by 11 dB compared to the reference state. This demonstrates the effectiveness of this DC voltage tuning-based optimization strategy in reducing the antenna's radar cross section.

[0060] Figure 11 This is a simulation diagram of the active beam modulation capability of the linearly polarized in-band co-polarized scattering reconfigurable array antenna provided in this embodiment of the invention at a frequency of 9 GHz and under the condition of phi-polarized vertical incidence. Figure 11 As shown, by precisely adjusting the capacitance value of each antenna element 1 in the array (i.e., changing its reflection phase), the main lobe direction of the scattered beam was successfully deflected from the initial 0° to 15°, 30°, and 45°, respectively. This demonstrates that the array antenna design possesses a powerful scattered beamforming capability. The result verifies that the array has a scattered beam deflection capability exceeding ±45°. This means that when electromagnetic waves are incident perpendicularly from the front, the array can guide its main scattered energy to a preset, non-mirror direction, which is one of the key mechanisms for achieving radar cross section (RCS) reduction and scattering "stealth." Figure 11The combined results show that this array antenna achieves active and flexible control of the scattered wavefront through digital coding or adjustable elements (such as the varactor diode 174). This capability allows the array to dynamically manipulate its own scattering characteristics.

[0061] Figure 12 This is a simulation result of the radiation gain pattern of the linearly polarized in-band co-polarized scattering reconfigurable array antenna in the yoz plane (E-plane) at 9 GHz, according to an embodiment of the present invention. In the figure, the "reference" curve (i.e., the black dashed line) corresponds to the reference state without scattering mode control, and the "cancellation" curve (i.e., the red dashed line) corresponds to the operating state with scattering mode control. The simulation results show that when the scattering state is switched by adjusting the capacitance of antenna element 1, the radiation performance of the antenna remains highly stable. Figure 12 The black and red dashed lines in the diagram closely match in overall shape. The main lobe beam direction remains unchanged, the main lobe width remains consistent, and the side lobe structures are essentially identical, indicating that changes in the scattering state do not cause distortion in the radiation pattern. Throughout the entire observation plane, the radiation gain changes between the two states are very small. The maximum gain change is less than 1.5 dB, demonstrating that while achieving scattering control, the antenna's basic radiator performance is guaranteed, and its energy radiation efficiency is not significantly affected. In summary, this array antenna exhibits excellent electromagnetic functional reconfigurability and radiation performance stability when switching between different operating states, laying a solid foundation for its practical application in advanced radar, communication, and low-observable platforms.

[0062] Compared with the prior art, the beneficial effects of the present invention include:

[0063] 1. Achieved efficient decoupling and independent control of radiation and scattering performance: This scheme separates radiation and scattering control performance through a multi-layer resonator structure, providing a stable benchmark for the antenna's radiation characteristics (such as impedance matching and radiation pattern). The good consistency between antenna elements and the integrated feeding method ensure that the array maintains stable and efficient radiation performance under various scattering conditions; furthermore, the reflection phase of each antenna element can be precisely controlled by changing the DC bias, thus achieving flexible reconstruction of the scattered wavefront without interfering with the antenna's normal radiation function. This effectively solves the core problem of the mutual constraint between scattering control and radiation performance in traditional designs.

[0064] 2. Compact structure and high integration: The antenna adopts a multi-layer stacked integrated design, vertically integrating the through-hole SMP connector, resonator structure, and reflective phase shifter. This three-dimensional integration method greatly improves space utilization and avoids the complex feeding structure and additional space occupation caused by traditional external phase shifting networks, making the antenna system structure simpler and more compact.

[0065] 3. Flexible and diverse scattering control: Based on the electronic tuning method of semiconductor devices, the equivalent scattering field distribution of the entire array can be changed rapidly and continuously within milliseconds by controlling the bias voltage of each antenna element through programming. This enables the antenna to dynamically generate multiple scattering modes (such as beam deflection, scattering diffusion, etc.), realizing a leap from "single fixed" to "multi-state reconfigurable", and has stronger environmental adaptability.

[0066] The above description, in conjunction with specific preferred embodiments, provides a further detailed explanation of the present invention. It should not be construed that the specific implementation of the present invention is limited to these descriptions. For those skilled in the art, various simple deductions or substitutions can be made without departing from the concept of the present invention, and all such modifications and substitutions should be considered within the scope of protection of the present invention.

Claims

1. A reconfigurable array antenna with in-band co-polarization scattering, characterized in that, include: Antenna module, the antenna module comprising: Multiple antenna elements with the same structure arranged in an array (1), and All are positive integers; Each antenna element (1) includes: A radiation patch (11), a first dielectric substrate (12), a metal patch (13), a second dielectric substrate (14), a metal ground plane (15), and a third dielectric substrate (16) are stacked sequentially from top to bottom in the z-direction. Along the x-direction, a plurality of metallized vias (121) are equally spaced at the center line of the first dielectric substrate (12) for contacting the metal patch (13), thereby forming a resonator structure together with the metal patch (13) and the metal ground plane (15); Each antenna unit (1) further includes: a reflective phase shifter (17); the reflective phase shifter (17) includes a microstrip transmission line (171), and a feed metal post (172), a metal short-circuit post (173), and a varactor diode (174) disposed on the microstrip transmission line (171); The feeding metal post (172) passes through the first through hole and contacts the radiating patch (11). The first through hole sequentially passes through the third dielectric substrate (16), the metal ground plane (15), the second dielectric substrate (14), the first dielectric substrate (12), and the radiating patch (11). The metal short-circuit post (173) passes through the second through hole and contacts the metal ground plane (15). The second through hole passes through the third dielectric substrate (16). The varactor diode (174) is connected to an external control unit through a DC bias line (2) to change its own DC bias voltage in response to the control signal sent by the external control unit, thereby changing the reflection phase of the scattered field of each antenna element (1) and realizing the reconfigurable scattering function of the antenna.

2. The linearly polarized band in-band co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, The microstrip transmission line (171) includes a first microstrip line (1711), a second microstrip line (1712), and a third microstrip line (1713), which form an "L" shape; the varactor diode (174) includes a first varactor diode (1741) and a second varactor diode (1742); the metal shorting post (173) includes a first shorting post (1731) and a second shorting post (1732); Along the x-direction, the first connection end of the first microstrip line (1711) is provided with the feeding metal post (172), the second connection end of the first microstrip line (1711) is connected to the negative terminal of the first varactor diode (1741), the positive terminal of the first varactor diode (1741) is connected to one end of the second microstrip line (1712), and the other end of the second microstrip line (1712) is provided with the first short-circuit post (1731). Along the y-direction, the third connection terminal of the first microstrip line (1711) is connected to the negative terminal of the second varactor diode (1742), the positive terminal of the second varactor diode (1742) is connected to one end of the third microstrip line (1713), and the other end of the third microstrip line (1713) is provided with the second short-circuit post (1732).

3. The linearly polarized band-co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, Each antenna unit (1) further includes: a through-hole SMP connector (18); the through-hole SMP connector (18) and the reflective phase shifter (17) are equidistant from the center line of the first dielectric substrate (12) in the y direction; The probe of the through-hole SMP connector (18) passes through the third through hole and contacts the radiating patch (11). The third through hole passes through the third dielectric substrate (16), the metal ground plane (15), the second dielectric substrate (14), the metal patch (13), the first dielectric substrate (12), and the radiating patch (11) in sequence.

4. The linearly polarized band in-band co-polarized scattering reconfigurable array antenna according to claim 3, characterized in that, Along the y-direction, the length of the metal patch (13) is less than the distance between the through-hole SMP connector (18) and the reflective phase shifter (17).

5. The linearly polarized band in-band co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, Also includes: The first group of pin headers (3) and the second group of pin headers (4) have the same structure; the first group of pin headers (3) and the second group of pin headers (4) are respectively arranged on two symmetrical sides of the antenna module along the x direction; Multiple sets of DC bias lines (2) are connected between the first set of pin headers (3) and the second set of pin headers (4) to connect to the external control unit through the first set of pin headers (3) and the second set of pin headers (4); Each set of DC bias lines (2) is connected to multiple antenna elements (1) through multiple inductors (5), with one inductor (5) corresponding to one antenna element (1).

6. The linearly polarized band in-band co-polarized scattering reconfigurable array antenna according to claim 5, characterized in that, The first group of pins (3) or the second group of pins (4) includes multiple groups of metal pins spaced apart, each group of metal pins corresponding to a set of DC bias lines (2).

7. The linearly polarized band-co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, The antenna module also includes... Threaded holes arranged in an array, and All are positive integers; along the x or y direction, each column of threaded holes is set between two adjacent groups of antenna elements (1) for threaded connection with plastic screws and nuts (6).

8. The linearly polarized band in-band co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, The range of the reflection phase of the scattered field of each antenna element (1) is 0°~300°.

9. The linearly polarized band in-band co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, and The value of is 8.

10. The linearly polarized band-co-polarized scattering reconfigurable array antenna according to claim 1, characterized in that, The number of metallized vias (121) is 11.

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