A harmonic suppression method and device for an AI computing power powered energy storage device transformer

Abstract

The present application relates to the technical field of transformers, and discloses a harmonic suppression method and device for an AI computing power power supply energy storage equipment transformer. The method comprises the following steps: obtaining the current of the primary side of the transformer and calculating the characteristic harmonic amplitude data injected into the primary side of the transformer when the GPU server switching power supply is in parallel operation and the phase angle difference parameters of the multi-split winding; introducing the phase angle difference between the windings for each split winding and arranging the turns ratio, so that the low-order characteristic harmonic currents are mutually canceled when they are converted to the primary side of each split winding and superimposed, and the residual amount of the harmonic currents after mutual cancellation is obtained; through the active harmonic compensation unit integrated in the transformer, high-order harmonic components are extracted, and a first compensation current with the same amplitude and opposite phase as the high-order harmonic components is injected into the common node of the transformer winding. The present application realizes stable suppression of the total harmonic current distortion rate of the transformer side under the full working condition of AI computing power.

Description

Technical Field

[0001] This invention relates to the field of transformer technology, and in particular to a harmonic suppression method and apparatus for a transformer used in AI computing power energy storage equipment. Background Technology

[0002] With the continuous growth in demand for AI computing power, large-scale parallel operation of switching power supplies for data center GPU servers has become the mainstream power supply method. When operating in parallel, the rectifier front end of the GPU server switching power supply continuously injects a large number of characteristic harmonic currents, mainly the 5th, 7th, 11th, and 13th harmonics, as well as higher harmonic currents above the 17th order, into the primary side of the power supply transformer. This results in a significant increase in additional copper losses in the transformer windings, aggravated eddy current losses in the core, and a significant drop in the actual operating efficiency of the transformer compared to the rated value, with a prominent problem of excessive temperature rise.

[0003] To address the aforementioned harmonic issues, existing technologies typically employ a single-winding transformer coupled with an external active filter. However, in these existing technologies, the single-winding transformer itself offers no suppression capability for harmonic currents; the entire harmonic current flows through the core magnetic circuit. The external active filter must cover the full frequency band of harmonics from the 5th to the 19th orders, requiring a large rated current capacity and a significant external installation volume relative to the transformer's main volume. Furthermore, external wiring impedance exists between the external active filter and the transformer, causing losses in the compensation current transmission path. Compensation accuracy is affected by line parameters, resulting in unstable overall harmonic suppression performance. Existing technologies cannot achieve harmonic suppression at the transformer body level and lack a layered harmonic suppression architecture that combines passive cancellation with active compensation. This makes it difficult to simultaneously meet the full-frequency suppression requirements for both low-order and high-order harmonics without increasing the transformer's main volume. Summary of the Invention

[0004] The main objective of this invention is to provide a harmonic suppression method and device for transformers used in AI computing power energy storage devices. This invention solves the technical problems of existing single-winding transformers combined with external active filter devices in AI computing power power supply scenarios, such as large size, high cost, and compensation accuracy affected by external connection impedance.

[0005] To achieve the above objectives, the present invention provides a harmonic suppression method for a transformer used in AI computing power energy storage equipment, comprising the following steps: Obtain the current on the primary side of the transformer and calculate the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. Based on the phase angle difference parameter, the phase angle difference between windings is introduced into each split winding and the turns ratio is arranged so that the low-order characteristic harmonic currents cancel each other out when the split windings are superimposed on the primary side and the residual amount of harmonic current after mutual cancellation is obtained. Based on the characteristic harmonic amplitude data and the residual harmonic current, the higher harmonic components are extracted by the active harmonic compensation unit integrated in the transformer, and a first compensation current with the same amplitude and opposite phase to the higher harmonic components is injected into the common node of the transformer winding.

[0006] Optionally, in a first implementation of the first aspect of the present invention, after injecting a first compensation current with equal amplitude and opposite phase to the higher harmonic components into the common node of the transformer winding, the method further includes: Calculate the total harmonic current distortion rate on the primary side of the transformer; When the total harmonic distortion rate does not exceed the set limit, the passive cancellation state of each split winding is maintained and the active harmonic compensation unit is kept in the first compensation bandwidth. When the total harmonic current distortion rate exceeds the set limit, the split windings and the active harmonic compensation unit are adjusted in coordination until the total harmonic current distortion rate drops below the set limit.

[0007] Optionally, in a second implementation of the first aspect of the present invention, the step of coordinating the adjustment of each split winding and the active harmonic compensation unit when the total harmonic current distortion exceeds a set limit, until the total harmonic current distortion drops below the set limit, includes: When the total distortion rate of the harmonic current exceeds the set limit, the set of excessive harmonic orders is obtained; Based on the set of out-of-standard harmonic orders, the lower edge of the second compensation bandwidth of the active harmonic compensation unit is extended to the frequency corresponding to the lowest harmonic order in the set of out-of-standard harmonic orders, and an extended compensation current command covering the set of out-of-standard harmonic orders is generated. The extended compensation current command is input into the PWM inverter for modulation, and a second compensation current is injected into the common node of the transformer winding through the injection transformer until the total distortion rate of the harmonic current drops to within the set limit, and the active harmonic compensation unit is restored to the standard compensation bandwidth.

[0008] Optionally, in a third implementation of the first aspect of the present invention, the step of acquiring the current on the primary side of the transformer and calculating the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel includes: The current on the primary side of the transformer is obtained, and a discrete Fourier transform is performed on the current on the primary side of the transformer to obtain the characteristic harmonic amplitude data of the 5th, 7th, 11th, 13th, 17th and 19th harmonics. Based on the characteristic harmonic amplitude data, the target harmonic order that needs to be passively canceled is determined and the phase angle difference parameters of each split winding are derived.

[0009] Optionally, in a fourth implementation of the first aspect of the present invention, determining the target harmonic order to be passively canceled based on the characteristic harmonic amplitude data and deriving the phase angle difference parameters of each split winding includes: Calculate the proportion of each harmonic amplitude to the fundamental amplitude in the characteristic harmonic amplitude data, and determine the harmonic number whose proportion exceeds the proportion threshold as the target harmonic number; Substituting the target harmonic number into the cancellation condition that the product of each target harmonic number and the phase angle difference is equal to an odd multiple of 180°, the phase angle difference parameters of each split winding are obtained.

[0010] Optionally, in a fifth implementation of the first aspect of the present invention, the step of introducing an inter-winding phase angle difference for each split winding based on the phase angle difference parameter and arranging the turns ratio so that the low-order characteristic harmonic currents cancel each other out when superimposed on the primary side of each split winding and obtaining the residual amount of the harmonic current after mutual cancellation includes: Based on the phase angle difference parameter, a phase angle difference between windings is introduced for each split winding, so that the low-order characteristic harmonic currents cancel each other out when the split windings are superimposed on the primary side. The low-order characteristic harmonic currents are characteristic harmonic currents of the 5th to 13th order. Based on the relative deviation of the amplitude of the low-order characteristic harmonic current in each split winding relative to the corresponding target harmonic current reference amplitude, the equivalent turns ratio correction ratio of each split winding referred to the primary side is calculated; and within the allowable turns ratio deviation range of the split winding, the turns ratio correction amount of each split winding is determined. The turns ratio of each split winding is arranged according to the turns ratio correction amount, and the residual harmonic current after mutual cancellation is obtained.

[0011] Optionally, in a sixth implementation of the first aspect of the present invention, the step of arranging the turns ratios of each split winding according to the turns ratio correction amount and obtaining the residual harmonic current after mutual cancellation includes: The rated turns ratio of each split winding is added together with the turns ratio correction amount to obtain the actual turns ratio of each split winding; Based on the actual turns ratio, the low-order characteristic harmonic currents in each split winding are converted to the primary side according to the actual turns ratio and then vector superimposed to obtain the residual harmonic current after the low-order characteristic harmonic currents cancel each other out.

[0012] Optionally, in a seventh implementation of the first aspect of the present invention, the step of extracting higher-order harmonic components based on the characteristic harmonic amplitude data and the residual harmonic current, through an active harmonic compensation unit integrated within the transformer, and injecting a first compensation current with equal amplitude and opposite phase to the higher-order harmonic components into the common node of the transformer windings, includes: Obtain the compensation priority and compensation amplitude constraints corresponding to the residual harmonic current, and perform Clarke transformation on the three-phase current of the primary side of the transformer to obtain the two-phase current components in the stationary coordinate system. A low-pass filter with a cutoff frequency lower than the 5th harmonic frequency is applied to the two-phase current components to separate the fundamental component; after subtracting the two-phase current components from the fundamental component, a bandpass filter covering the 17th to 19th harmonic frequency range is applied to extract the 17th and 19th higher harmonic components. Based on the higher harmonic components and the current conversion relationship of the injected transformer, a compensation current command that is inversely related to the higher harmonic components at the common node of the transformer winding is generated, and the first compensation current is output through the PWM inverter in the active harmonic compensation unit and coupled to the common node of the transformer winding via the injected transformer.

[0013] Optionally, in an eighth implementation of the first aspect of the present invention, the step of generating a compensation current command that is inversely related to the higher harmonic components at the common node of the transformer winding based on the current conversion relationship between the higher harmonic components and the injected transformer, and outputting a first compensation current through the PWM inverter in the active harmonic compensation unit, and coupling it to the common node of the transformer winding via the injected transformer, includes: Based on the higher harmonic components, a proportional resonant controller with the corresponding harmonic frequency as the resonant frequency is configured for each higher harmonic frequency; the proportional resonant controller performs frequency selective tracking of the higher harmonic components, and combines the phase compensation parameters, the injection transformer conversion factor and the PWM inverter current limit to obtain a compensation current command that is opposite to the corresponding higher harmonic component at the common node of the transformer winding. The compensation current command is input to the PWM inverter in the active harmonic compensation unit integrated in the transformer for modulation to obtain the first compensation current, which is then injected into the common node of the transformer winding after being coupled through the transformer.

[0014] The present invention also provides a harmonic suppression device for a transformer used in an AI computing power energy storage device, comprising: The calculation module is used to obtain the current on the primary side of the transformer and calculate the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. The mutual cancellation module is used to introduce the inter-winding phase angle difference for each split winding and arrange the turns ratio based on the phase angle difference parameter, so that the low-order characteristic harmonic currents cancel each other when the split windings are superimposed on the primary side and obtain the residual amount of harmonic current after mutual cancellation. The compensation module is used to extract higher harmonic components based on the characteristic harmonic amplitude data and the residual harmonic current, through an active harmonic compensation unit integrated in the transformer, and inject a first compensation current with the same amplitude and opposite phase to the higher harmonic components into the common node of the transformer winding.

[0015] In summary, this invention introduces precise inter-winding phase angle differences for each split winding and combines this with turns ratio arrangement, enabling low-order characteristic harmonic currents to cancel each other out when superimposed on the primary side of each split winding. This eliminates the contribution of the main characteristic harmonics to core eddy current losses and additional copper losses in the windings at the transformer's magnetic circuit level, achieving significant suppression of low-order main harmonics without the need for external filtering devices. This invention integrates a small-capacity active harmonic compensation unit inside the transformer body, implementing real-time active cancellation of the 17th and 19th harmonics that cannot be covered by passive cancellation mechanisms. The compensation current is directly coupled to the common node of the transformer windings via the injection transformer, eliminating the influence of external connection impedance on compensation accuracy. Since the passive cancellation layer has already significantly eliminated the 5th to 13th main harmonics, the active compensation unit only needs to handle the residual high-order harmonics. Its rated capacity is significantly reduced compared to existing external active filtering devices, meeting the constraint of integrating it inside the transformer body without increasing the overall volume. This invention achieves stable suppression of the total harmonic current distortion rate on the transformer side under all operating conditions of AI computing power by continuously monitoring and dynamically scheduling the total harmonic current distortion rate in a hierarchical manner, and automatically expanding the active compensation bandwidth to take over the passive cancellation of insufficient harmonic numbers under sudden load changes of GPU servers, thus significantly restoring the overall operating efficiency of the transformer. Attached Figure Description

[0016] Figure 1 This is a schematic diagram of the harmonic suppression method for a transformer used in an AI computing power energy storage device according to an embodiment of the present invention; Figure 2 This is a schematic diagram illustrating the steps of coordinated adjustment between each split winding and the active harmonic compensation unit in an embodiment of the present invention; Figure 3 This is a schematic diagram illustrating the steps for calculating characteristic harmonic amplitude data and phase angle difference parameters in an embodiment of the present invention; Figure 4 This is a schematic diagram illustrating the steps of harmonic current cancellation in an embodiment of the present invention; Figure 5 This is a schematic diagram of the steps for high-order harmonic current compensation in an embodiment of the present invention; Figure 6 This is a structural block diagram of a harmonic suppression device for a transformer used in an AI computing power energy storage device according to an embodiment of the present invention; Figure 7 This is a schematic diagram illustrating the application of a transformer for AI computing power supply and energy storage equipment in an embodiment of the present invention.

[0017] The realization of the objective, functional features and advantages of the present invention will be further explained in conjunction with the embodiments and with reference to the accompanying drawings. Detailed Implementation

[0018] To make the objectives, technical solutions, and advantages of this invention clearer, the invention will be further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative and not intended to limit the invention.

[0019] Reference Figure 1 This embodiment provides a harmonic suppression method for transformers used in AI computing power energy storage devices, including the following steps: S10: Obtain the current on the primary side of the transformer and calculate the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. S20, based on the phase angle difference parameter, introduces the phase angle difference between windings for each split winding and arranges the turns ratio so that the low-order characteristic harmonic currents cancel each other out when the split windings are superimposed on the primary side and obtains the residual amount of harmonic current after mutual cancellation. S30, based on characteristic harmonic amplitude data and residual harmonic current, extracts high-order harmonic components through an active harmonic compensation unit integrated in the transformer, and injects a first compensation current with equal amplitude and opposite phase to the high-order harmonic components into the common node of the transformer winding.

[0020] In this embodiment of the invention, by introducing a precise inter-winding phase angle difference for each split winding and combining it with the turns ratio arrangement, the low-order characteristic harmonic currents cancel each other out when superimposed on the primary side of each split winding. This eliminates the contribution of the main characteristic harmonics to the core eddy current loss and the additional copper loss of the windings at the transformer body magnetic circuit level, achieving significant suppression of low-order main harmonics without the need for an external filter. This invention integrates a small-capacity active harmonic compensation unit inside the transformer body, implementing real-time active cancellation of the 17th and 19th higher harmonics that cannot be covered by passive cancellation mechanisms. The compensation current is directly coupled to the common node of the transformer windings via the injection transformer, eliminating the influence of external connection impedance on the compensation accuracy. Since the passive cancellation layer has already significantly eliminated the 5th to 13th main harmonics, the active compensation unit only needs to handle the residual amount of higher harmonics. Its rated capacity is significantly reduced compared to existing external active filter devices, meeting the constraint of integrating it inside the transformer body without increasing the main body volume. This invention achieves stable suppression of the total harmonic current distortion rate on the transformer side under all operating conditions of AI computing power by continuously monitoring and dynamically scheduling the total harmonic current distortion rate in a hierarchical manner, and automatically expanding the active compensation bandwidth to take over the passive cancellation of insufficient harmonic numbers under sudden load changes of GPU servers, thus significantly restoring the overall operating efficiency of the transformer.

[0021] In a specific example, such as Figure 2 After injecting a first compensation current of equal amplitude and opposite phase to the higher harmonic components into the common node of the transformer windings, the process also includes: S40, calculate the total harmonic current distortion rate on the primary side of the transformer; S50, when the total harmonic current distortion rate does not exceed the set limit, maintain the passive cancellation state of each split winding and keep the active harmonic compensation unit in the first compensation bandwidth. S60: When the total harmonic current distortion rate exceeds the set limit, the split windings and active harmonic compensation units are adjusted in a coordinated manner until the total harmonic current distortion rate drops below the set limit.

[0022] In this embodiment, three-phase current is continuously collected at the common busbar on the primary side of the transformer, and the effective values ​​of the fundamental current and the 2nd to 19th harmonic currents are extracted by discrete Fourier transform. The total harmonic current distortion rate is calculated according to the following formula: in, This represents the total distortion rate of harmonic current on the primary side of the transformer, expressed as a percentage. This represents the effective value of the fundamental current, in amperes. Indicates the first The effective value of the second harmonic current, in amperes; This indicates the harmonic order. When the total harmonic current distortion rate calculated in real time does not exceed the set limit (5%), it indicates that the passive cancellation effect of the multi-split phase-shifting winding on the 5th to 13th main characteristic harmonics is within the effective range. At the same time, the compensation amount of the active harmonic compensation unit for the 17th and 19th higher harmonics can maintain the harmonic level stability of the common bus on the primary side of the transformer. At this time, the controller does not change the phase angle difference and turns ratio arrangement of each split winding, and still maintains the passive cancellation of each split winding according to the predetermined phase relationship, and keeps the active harmonic compensation unit in the first compensation bandwidth. The first compensation bandwidth is set to 850Hz to 950Hz, corresponding to the 17th and 19th higher harmonics under the 50Hz fundamental frequency. In the actual digital filtering implementation, the passband of the bandpass filter is set to 800Hz to 1000Hz, so that the filter boundary covers the 17th and 19th higher harmonics, while retaining a certain frequency margin to adapt to the attenuation effect caused by the small shift of the grid frequency and the filter transition band. At this time, the active harmonic compensation unit only outputs the first compensation current with the same amplitude and opposite phase as the higher harmonic components, without intervening in the compensation of the main characteristic harmonics from the 5th to the 13th order, thus avoiding the active compensation unit bearing too large a low-order harmonic current capacity.

[0023] In this embodiment, when the total harmonic distortion rate of the real-time harmonic current exceeds the set limit (5%), the controller determines the primary side common bus of the transformer to be in a harmonic over-limit state and triggers the coordinated adjustment between each split winding and the active harmonic compensation unit. The coordinated scheduling is based on the identification of the operating status, the location of the over-limit harmonic order, the expansion of the compensation bandwidth, and the allocation of the compensation current limit. Under the condition that the predetermined phase shift structure and turns ratio configuration of each split winding remain unchanged, the passive cancellation layer continues to bear the basic suppression function of the 5th to 13th harmonics, while the active harmonic compensation unit temporarily compensates for the residual harmonics formed by insufficient passive cancellation. After the total harmonic distortion rate exceeds the limit, the controller extracts the proportion of each harmonic current to the fundamental current, and combines it with the vector superposition result of the same harmonic current collected at the output terminals of each split winding to determine whether the source of the over-limit is from the increase of the 17th and 19th higher harmonics, or from the decrease in the passive cancellation rate of the 5th to 13th harmonics due to a sudden change in load. If the over-limit mainly originates from higher harmonics, the active harmonic compensation unit maintains the higher harmonic compensation range and increases the compensation current amplitude at the corresponding frequency. If the over-limit mainly originates from lower frequency residual harmonics such as the 13th or 11th harmonics, the controller temporarily lowers the lower edge of the compensation bandwidth, for example, to 650Hz to cover the 13th harmonic, allowing the active harmonic compensation unit to take over the passive cancellation of insufficient residual quantities within the limited current capacity. During the coordinated adjustment, the output current of the PWM inverter needs to be constrained by the rated compensation current, and the rated compensation current of the active harmonic compensation unit can be set to 12% of the transformer's rated current. As the compensation bandwidth expands and the compensation current injection continues, the controller continues to calculate the total harmonic current distortion rate at a 10ms cycle. When the total harmonic current distortion rate recovers to within 5% and remains stable for several refresh cycles, the active harmonic compensation unit is restored to the first compensation bandwidth, and the passive cancellation state of each split winding continues to be maintained.

[0024] In a specific example, S60 includes: When the total harmonic distortion rate exceeds the set limit, obtain the set of harmonic orders that exceed the limit; Based on the set of out-of-standard harmonic orders, the lower edge of the second compensation bandwidth of the active harmonic compensation unit is extended to the frequency corresponding to the lowest harmonic order in the set of out-of-standard harmonic orders, and an extended compensation current command covering the set of out-of-standard harmonic orders is generated. The extended compensation current command is input to the PWM inverter for modulation, and the second compensation current is injected into the common node of the transformer winding through the injection transformer until the total harmonic current distortion rate drops to within the set limit, and the active harmonic compensation unit is restored to the standard compensation bandwidth.

[0025] In this embodiment, the controller reads the effective values ​​of each harmonic current on the primary side common bus of the transformer in each 10ms refresh cycle, and compares the real-time total harmonic current distortion rate with a set limit of 5%. After the total harmonic current distortion rate exceeds 5%, the controller does not directly change the phase angle difference and turns ratio arrangement already formed by the multi-split windings, but continues to maintain the passive cancellation state of the split windings, and calculates the residual proportion of the 5th, 7th, 11th, 13th, 17th and 19th harmonics one by one, and writes the harmonic number with the residual proportion exceeding the corresponding limit into the set of excessive harmonic number.

[0026] In this embodiment, the controller reads the lowest harmonic order from the set of out-of-standard harmonic orders and calculates the corresponding frequency based on the 50Hz fundamental frequency. When the lowest out-of-standard harmonic order is 13, the corresponding frequency is 650Hz, and the lower edge of the second compensation bandwidth shifts from the standard high-order compensation range to 650Hz. When the lowest out-of-standard harmonic order is 17, the second compensation bandwidth remains around 850Hz, still mainly processing the 17th and 19th high-order harmonics. The upper edge of the second compensation bandwidth can be maintained at 950Hz, and a certain transition margin is reserved in the digital bandpass filter implementation, so that the extended compensation current command can cover all harmonic components in the set of out-of-standard harmonic orders. In this embodiment, the digital signal processor generates extended compensation current commands according to the amplitude, phase, and compensation priority of each out-of-standard harmonic. The extended compensation current commands maintain an equal amplitude and opposite phase relationship with the corresponding residual harmonic currents and are constrained by the rated compensation current of the active harmonic compensation unit. When the compensation capacity is insufficient to cover all out-of-standard harmonics at the same time, priority is given to compensating the low-order residual harmonics that contribute significantly to the total distortion rate of the harmonic current, while retaining the basic compensation components of the 17th and 19th higher harmonics.

[0027] In this embodiment, after the extended compensation current command is input to the PWM inverter, the PWM inverter outputs a modulation pulse according to the current closed loop, driving the three-phase full-bridge power devices to generate a second compensation current. The second compensation current is coupled to the common node of the transformer windings through the injection transformer, so that the residual harmonic current at the common node is canceled in the reverse direction. During the compensation injection, the controller continuously monitors the total harmonic current distortion rate; after the total harmonic current distortion rate is lower than 5% for three consecutive refresh cycles, the harmonic over-limit state is determined to be lifted, and the active harmonic compensation unit is restored from the second compensation bandwidth to the standard compensation bandwidth, so that the active harmonic compensation unit re-concentrates on compensating the 17th and 19th high-order harmonics, avoiding excessive current capacity occupancy of the inverter due to prolonged extended low-frequency compensation.

[0028] In a specific example, such as Figure 3 The process involves acquiring the primary current of the transformer and calculating the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. S11: Obtain the current on the primary side of the transformer and perform a discrete Fourier transform on the current on the primary side of the transformer to obtain the characteristic harmonic amplitude data of the 5th, 7th, 11th, 13th, 17th and 19th harmonics. S12, based on characteristic harmonic amplitude data, determines the target harmonic order that needs to be passively canceled and derives the phase angle difference parameters of each split winding.

[0029] In this embodiment, a broadband current transformer is arranged at the common bus on the primary side of the transformer to synchronously sample the three-phase current. The collected three-phase time-domain currents are filtered for anti-aliasing and periodically truncated to establish a data window. The current sequence within the data window is subjected to a discrete Fourier transform to extract the effective values ​​and phase information of the fundamental frequency and each target harmonic frequency. Since the rectifier front end of the GPU server switching power supply exhibits a six-pulse rectification characteristic, the primary side of the transformer is more likely to have characteristic harmonics such as the 5th, 7th, 11th, 13th, 17th, and 19th harmonics. Therefore, spectrum analysis does not need to process all frequency points indiscriminately, but focuses on these characteristic harmonic orders to form characteristic harmonic amplitude data containing the amplitude, phase angle, and relative proportion of each harmonic to the fundamental frequency. Although the 3rd, 9th, and 15th zero-sequence harmonics can be identified during sampling and spectral decomposition, these zero-sequence components can form internal circulating paths through delta-connected or zigzag-connected windings. Therefore, these zero-sequence components are not the primary targets for passive cancellation by phase-shifting windings.

[0030] In this embodiment, the controller calculates the ratio of each characteristic harmonic amplitude to the fundamental amplitude and determines the harmonics whose ratio exceeds a preset ratio threshold as the target harmonics to be passively canceled. When the 5th harmonic is about 15% to 20% of the fundamental, the 7th harmonic is about 10% to 15% of the fundamental, and the 11th and 13th harmonics still have significant loss contributions, the 5% ratio threshold can include the 5th to 13th harmonics in the passive cancellation targets; while the 17th and 19th harmonics do not exceed 5% of the fundamental and are more suitable as processing targets for the active harmonic compensation unit. After completing the target harmonic number screening, the controller determines the phase angle difference between windings based on the harmonic cancellation condition of the multi-split phase-shifting windings, so that the product of the target harmonic number and the phase angle difference between windings satisfies an odd multiple of 180°, so that the harmonic currents of the same order after being referred to the primary side by different split windings can cancel each other out of phase as much as possible when vector superimposed. If the target only covers the 5th and 7th harmonics, an equivalent 12-pulse configuration can be formed using a 30° phase angle difference. If the target harmonics further cover the 11th and 13th harmonics, three sets of split windings can be used to form a fundamental phase arrangement of 0°, 20°, and 40°, forming an equivalent 18-pulse phase-shifting structure. This allows the 5th, 7th, 11th, and 13th harmonics to form different phase rotation relationships according to their corresponding harmonic orders when referred to the primary side common bus. This reduces the combined amplitude of the main characteristic harmonics after vector superposition. The phase angle difference control accuracy can be set to ±0.5°. This accuracy is used to limit the phase deviation caused by the integerization of the number of turns in the extension winding or phase-shifting winding, and to avoid the phase deviation weakening the vector cancellation depth.

[0031] In a specific example, S12 includes: Calculate the proportion of each harmonic amplitude to the fundamental amplitude in the characteristic harmonic amplitude data, and determine the harmonic number whose proportion exceeds the proportion threshold as the target harmonic number; Substituting the target harmonic number into the cancellation condition that the product of each target harmonic number and the phase angle difference equals an odd multiple of 180°, the phase angle difference parameters of each split winding are obtained.

[0032] In this embodiment, after completing the discrete Fourier transform, the amplitudes of the 5th, 7th, 11th, 13th, 17th, and 19th harmonics are compared with the fundamental amplitude under the same amplitude reference to form a harmonic amplitude distribution matrix. For example, the ratios of the amplitudes of the 5th, 7th, 11th, 13th, 17th, and 19th harmonics to the fundamental amplitude together constitute the target judgment criteria. A proportional threshold of 5% is set to distinguish between the main characteristic harmonics that should be handled by the winding structure and the weaker higher-order harmonics that are more suitable for processing by the active harmonic compensation unit. In AI computing power supply load scenarios, the 5th harmonic is about 15% to 20% of the fundamental frequency, the 7th harmonic is about 10% to 15% of the fundamental frequency, the 11th and 13th harmonics still have a significant loss contribution, while the 17th and 19th higher-order harmonics do not exceed 5% of the fundamental frequency. Therefore, the 5% proportional threshold can screen the 5th to 13th harmonics as passive cancellation targets, and leave the 17th and 19th higher-order harmonics to be handled by the active compensation layer. After the controller completes the proportional value comparison, it writes the harmonic numbers exceeding the proportional threshold into the target harmonic number set, and confirms the target harmonic number set by combining the harmonic loss contribution ranking, avoiding the winding phase angle difference design deviating from the main loss source due to relying solely on instantaneous amplitude fluctuations.

[0033] In this embodiment, after the target harmonic order set is determined, the controller derives the phase angle difference between the windings based on the phase cancellation condition of the multi-pulse rectifier transformer. The cancellation condition can be expressed as: in, Represents the target harmonic order, dimensionless; This represents the fundamental phase angle difference between split windings, expressed in degrees. This represents a positive integer sequence number, used to indicate odd multiples of 180°. When the 5th, 7th, 11th, and 13th harmonics all fall within the target harmonic order set, the controller selects a multi-split phase-shifting structure that can accommodate multiple main characteristic harmonics. When the target only covers the 5th and 7th harmonics, the phase angle difference between windings can be 30°, forming an equivalent 12-pulse configuration. When the target extends to the 11th and 13th harmonics, the phase angle difference between windings is preferably 20°, with the three split windings corresponding to the fundamental phases of 0°, 20°, and 40°, forming an equivalent 18-pulse configuration. This ensures that the 5th, 7th, 11th, and 13th harmonics undergo vector cancellation after being referred to the primary side common bus. Since the passive cancellation focuses on the main characteristic harmonics from the 5th to the 13th, the phase angle difference parameter output by the controller is preferably a 20° arithmetic phase angle difference, and the controller simultaneously outputs the number of three split windings, the phase arrangement of each split winding, and the allowable deviation range of ±0.5° for the phase angle difference. ±0.5° is used to constrain the integerization of the number of turns in the extended winding, the difference in winding leakage flux, and the phase shift caused by manufacturing and assembly errors, so that the turn ratio arrangement and vector superposition calculation can maintain a relatively stable cancellation depth.

[0034] In a specific example, such as Figure 4 S20 includes: S21, based on the phase angle difference parameter, introduces the phase angle difference between each split winding, so that the low-order characteristic harmonic currents cancel each other out when the split windings are superimposed on the primary side. The low-order characteristic harmonic currents are the characteristic harmonic currents of the 5th to 13th orders. S22, based on the relative deviation of the amplitude of the low-order characteristic harmonic current in each split winding relative to the corresponding target harmonic current reference amplitude, calculate the equivalent turns ratio correction ratio of each split winding referred to the primary side; and within the allowable turns ratio deviation range of the split winding, determine the turns ratio correction amount of each split winding. S23, arrange the turns ratio of each split winding according to the turns ratio correction amount and obtain the residual amount of harmonic current after mutual cancellation.

[0035] In this embodiment, based on a 20° arithmetic phase angle difference, the number of three split windings, and the fundamental phase arrangement of 0°, 20°, and 40°, three sets of split windings are constructed on the secondary side of the transformer. Through star connection, extended delta connection, or winding connection with equivalent phase shift capability, the three sets of split windings form a predetermined phase difference on the fundamental side. Since the 5th, 7th, 11th, and 13th harmonics will undergo phase rotation corresponding to multiples of the fundamental phase difference when referred to the primary side common bus, after the output terminals of the three sets of split windings are connected to a GPU server switching power supply branch of similar capacity, the characteristic harmonic currents of the same order no longer exhibit in-phase superposition on the primary side, but instead form a mutual cancellation relationship in the vector plane. To reduce the impact of manufacturing errors on the vector cancellation depth, the allowable deviation of the winding phase shift angle can be controlled within ±0.5°, and the rounding error of the number of turns in the extended winding or phase-shifting winding is controlled to no more than 1 turn, ensuring a stable phase cancellation basis for the low-order characteristic harmonic currents when referred to the primary side.

[0036] In this embodiment, a turns ratio correction is introduced based on the phase cancellation structure. The controller collects the amplitudes of the 5th, 7th, 11th, and 13th harmonic currents at the output terminals of each split winding, and compares the amplitude of the same harmonic of each split winding with the corresponding target harmonic current reference amplitude. The target harmonic current reference amplitude can be the average of the amplitudes of multiple split windings at the same harmonic order. The average value can reflect the desired amplitude level when the load is relatively balanced. For split windings with amplitudes higher than the target harmonic current reference amplitude, the controller sets the equivalent turns ratio correction ratio to negative compensation; for split windings with amplitudes lower than the target harmonic current reference amplitude, the controller sets the equivalent turns ratio correction ratio to positive compensation, so that the harmonic currents in each split winding tend to the same amplitude reference after being converted to the primary side. The actual number of turns of the split winding is determined according to the following formula: in, Indicates the first The actual number of turns in the split winding, in turns; This indicates the rated number of turns of the split winding, in turns. Indicates the first The turns correction factor for split windings, dimensionless; This indicates the split winding number. The turns correction positive coefficient is limited to the range of [-0.05, +0.05], which corresponds to a process-adjustable range of ±5% of the rated turns. This allows for compensation of load distribution differences without compromising the transformer's rated voltage level and insulation structure. For scenarios where GPU server load rates vary between 30% and 100%, the controller can determine the turns correction amount for each split winding group based on the harmonic amplitude deviation at typical load points. It then compromises the correction results across multiple load points, ensuring good cancellation stability of the turns ratio arrangement under light load, rated load, and increasing load conditions.

[0037] In this embodiment, during the winding design, manufacturing, or tap position determination stage, the turns ratio configuration of each split winding is completed according to the determined turns ratio correction coefficient. During the operation stage, the controller does not change the already formed winding turns ratio structure, but instead converts the low-order characteristic harmonic currents in each split winding to the primary side common bus according to the actual turns ratio, and performs vector superposition. The remaining harmonic currents of the same order after vector superposition are used as the residual harmonic currents after mutual cancellation.

[0038] In a specific example, S23 includes: The rated turns ratio of each split winding is added together with the turns ratio correction to obtain the actual turns ratio of each split winding; Based on the actual turns ratio, the low-order characteristic harmonic currents in each split winding are converted to the primary side according to the actual turns ratio and then vector superimposed to obtain the residual harmonic current after the low-order characteristic harmonic currents cancel each other out.

[0039] In this embodiment, the controller uses the rated voltage level, rated capacity, and predetermined phase arrangement of each split winding as constraints to read the turns ratio correction amount and forms the actual turns ratio for each group of split windings within a ±5% allowable turns ratio deviation range. After the actual turns ratio is formed, the controller corrects the turns ratio to make the amplitude of the same harmonic current in each split winding, after being referred to the primary side, more consistent, thereby reducing the vector cancellation deviation caused by uneven load on the GPU server branch. For split windings with high harmonic current amplitude, the actual turns ratio is determined according to the negative correction result, which reduces the equivalent harmonic current amplitude referred to the primary side; for split windings with low harmonic current amplitude, the actual turns ratio is determined according to the positive correction result, which increases the equivalent harmonic current amplitude referred to the primary side. After processing, the 5th, 7th, 11th, and 13th harmonic currents superimposed at the common bus on the primary side of each split winding retain the phase difference generated by the phase-shifting winding and obtain closer amplitude conditions through turns ratio arrangement.

[0040] In this embodiment, when acquiring the residual harmonic current, the controller establishes vector superposition channels for the 5th, 7th, 11th, and 13th harmonics respectively. The same harmonic current detected by each set of split windings is converted to the primary side common bus according to the actual turns ratio, while retaining the corresponding harmonic phase angle. After conversion, the same harmonic current is synthesized in a vector form determined by both amplitude and phase. The amplitude of the synthesized result is the residual amount of the corresponding harmonic after mutual cancellation. If the amplitudes of the same harmonic currents in the three sets of split windings are relatively close, and the phase relationship meets the requirement of equal arithmetic phase shift, the vector synthesized amplitude will be less than the scalar sum of the amplitudes of the same harmonic currents in each split winding, indicating that passive cancellation is effective. If the synthesized amplitude is abnormally large, it indicates that the corresponding harmonic has problems such as load imbalance, phase shift, or insufficient turns ratio correction.

[0041] In a specific example, such as Figure 5 S30 includes: S31, obtain the compensation priority and compensation amplitude constraints corresponding to the residual harmonic current, and perform Clarke transformation on the three-phase current of the primary side of the transformer to obtain the two-phase current components in the stationary coordinate system. S32, apply a low-pass filter with a cutoff frequency lower than the 5th harmonic frequency to the two-phase current components to separate the fundamental component; after subtracting the two-phase current components from the fundamental component, apply a bandpass filter covering the 17th to 19th harmonic frequency range to extract the 17th and 19th higher harmonic components. S33 generates a compensation current command that is inversely related to the higher harmonic components and the current conversion relationship of the injected transformer based on the higher harmonic components. The first compensation current is output through the PWM inverter in the active harmonic compensation unit and coupled to the common node of the transformer winding via the injected transformer.

[0042] In this embodiment, after passive cancellation of the 5th to 13th harmonics, the residual current of each harmonic is read, and the compensation priority is determined based on the magnitude of the residual current, the harmonic order, and its contribution to the total distortion rate of the harmonic current. The 17th and 19th harmonics are difficult to eliminate sufficiently by the passive phase-shifting winding, so the 17th and 19th harmonics are given priority to enter the first compensation bandwidth. When the 5th to 13th harmonics have been suppressed to a low level by the multi-split phase-shifting winding, the rated compensation current of the active harmonic compensation unit can be constrained by 12% of the rated current of the transformer. This value matches the conservative superposition estimate of the amplitude of the 17th and 19th harmonics, which can limit the three-phase full-bridge PWM inverter from bearing excessive compensation current for a long time. After the compensation priority and compensation amplitude constraints are determined, the broadband current transformer collects three-phase current at the common bus on the primary side of the transformer. The sampling rate can be set to 100kHz, and the frequency response range covers 50Hz to 950Hz, ensuring sufficient frequency resolution for the 17th and 19th harmonics in the sampling link. The digital signal processor converts the three-phase sampled current into two-phase current components in a stationary coordinate system using Clarke transform. The three-phase AC quantities are thus converted into orthogonal current components that are easy to filter, decompose, and compensate for.

[0043] In this embodiment, the digital signal processor applies a digital low-pass filter to the two-phase current components in the stationary coordinate system. The cutoff frequency of the low-pass filter can be set to 150Hz. 150Hz is higher than the 50Hz fundamental frequency, preserving the main variation of the fundamental current, while being lower than 250Hz corresponding to the 5th harmonic, preventing the 5th and 19th harmonics from entering the fundamental component. After passive cancellation, the amplitudes of the 5th to 13th residual harmonics are significantly reduced, therefore the fundamental component obtained by the low-pass filter is less susceptible to significant interference from lower-order residual harmonics. In this embodiment, the digital signal processor subtracts the two-phase current components from the fundamental component obtained by the low-pass filter to obtain the harmonic current components after removing the fundamental harmonic. The calculation relationship can be expressed as: in, This represents the first-axis current component in the stationary coordinate system, with units of amperes. This represents the second-axis current component in the stationary coordinate system, with units of amperes. This represents the fundamental current component of the first axis, in amperes. This represents the fundamental current component of the second axis, in amperes. This represents the first axis harmonic current component, in amperes. This represents the second-axis harmonic current component, measured in amperes. After fundamental frequency rejection, the digital signal processor applies a bandpass filter to the harmonic current component, for example, set to 800Hz to 1000Hz, covering the 850Hz corresponding to the 17th harmonic and the 950Hz corresponding to the 19th harmonic, while retaining a certain transition band margin to accommodate small shifts in the grid frequency and attenuation at the digital filter edges. After processing, the 17th and 19th higher harmonic components are obtained, carrying amplitude and phase information.

[0044] In this embodiment, the digital signal processor generates a compensation current command based on the extracted higher harmonic components and the current conversion relationship of the injected transformer. Since the injected transformer can adopt a 1:1 turns ratio coupling structure, the current conversion relationship is relatively direct when the compensation current is coupled from the output of the three-phase full-bridge PWM inverter to the common node of the transformer winding. The controller mainly needs to compensate for the phase delay caused by sampling, filtering, calculation, and PWM modulation, so that the first compensation current at the common node of the winding maintains an equal amplitude and anti-phase relationship with the higher harmonic components. After the compensation current command is input to the PWM inverter, the three-phase full-bridge power devices output modulation pulses according to the current closed loop and generate the corresponding compensation current. The compensation current is coupled to the common node of the transformer winding through the injected transformer and cancels out the 17th and 19th higher harmonic currents at the common node. Since the compensation current transmission path is located inside the transformer body, the influence of the external connection impedance on the compensation accuracy is weakened. The active harmonic compensation unit only bears the high-order residual components that are difficult to cover by the passive cancellation layer, thus forming a continuous cooperation between the low-order passive suppression capability of the multi-split winding and the high-order active suppression capability of the integrated compensation unit.

[0045] In a specific example, S33 includes: Based on the higher harmonic components, a proportional resonant controller with the corresponding harmonic frequency as the resonant frequency is configured for each higher harmonic frequency. The proportional resonant controller performs frequency selective tracking of the higher harmonic components, and combined with the phase compensation parameters, the injection transformer conversion factor and the PWM inverter current limit, a compensation current command that is opposite to the corresponding higher harmonic component at the common node of the transformer winding is obtained. The compensation current command is input to the PWM inverter in the active harmonic compensation unit integrated in the transformer for modulation to obtain the first compensation current, which is then injected into the common node of the transformer winding after being coupled through the transformer.

[0046] In this embodiment, after extracting the 17th and 19th harmonic components, the digital signal processor establishes independent proportional resonant control channels according to different harmonic frequencies. Each channel has a high gain only for harmonic current errors near its corresponding frequency. For example, under a 50Hz fundamental frequency, the 17th harmonic corresponds to 850Hz, and the 19th harmonic corresponds to 950Hz. The proportional resonant controller sets its resonant center around these frequencies to selectively track the higher harmonic components. The controller uses the extracted higher harmonic components as the objects to be canceled and takes the required anti-phase current at the winding common node as the control target. When generating the compensation current command, the controller synchronously introduces phase compensation parameters to compensate for the time delays caused by sampling, filtering, calculation, and PWM modulation, ensuring that the compensation current maintains an anti-phase relationship with the corresponding higher harmonic component when it reaches the winding common node. When the injection transformer adopts a 1:1 turns ratio coupling structure, the injection transformer conversion factor can be taken as 1. If other coupling turns ratios are used, the controller needs to convert the PWM inverter output current command according to the injection transformer conversion factor to ensure that the actual injected current at the winding common node meets the compensation amplitude requirements. At the same time, the PWM inverter current limit is set according to the rated compensation current of the active harmonic compensation unit. The rated compensation current can be set to 12% of the transformer rated current. This value corresponds to the conservative superposition estimate of the amplitudes of the 17th and 19th harmonics, which can limit the long-term overload operation of the integrated compensation unit.

[0047] In this embodiment, after the compensation current command is generated, the digital signal processor synthesizes the components output from each proportional resonant control channel and performs current limiting, phase correction, and PWM modulation duty cycle conversion to obtain the switching drive signal for the three-phase full-bridge PWM inverter. The PWM inverter can use silicon carbide power devices, and the switching frequency is set to 100kHz, making the inverter switching frequency much higher than the highest target compensation frequency of 950Hz, thereby reducing the impact of modulation ripple on the accuracy of high-order harmonic compensation. The first compensation current output by the three-phase full-bridge PWM inverter is coupled to the common node of the transformer winding through the injection transformer. At the common node, it forms an anti-phase superposition with the 17th and 19th high-order harmonic currents, reducing the residual high-order harmonics flowing from the common node to the primary side. During the compensation injection process, the digital signal processor continues to read the primary side common bus current and performs closed-loop correction on the compensated harmonic components. When the residual of a certain harmonic frequency is still too high, the corresponding proportional resonant control channel increases the compensation output at that frequency. When the residual decreases to within the amplitude constraint range, the corresponding channel maintains a smaller compensation output.

[0048] Reference Figure 6 This embodiment provides a harmonic suppression device for a transformer used in AI computing power energy storage equipment, comprising: Calculation module 601 is used to obtain the current on the primary side of the transformer and calculate the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. The mutual cancellation module 602 is used to introduce the inter-winding phase angle difference and arrange the turns ratio of each split winding based on the phase angle difference parameter, so that the low-order characteristic harmonic currents can cancel each other when the split windings are superimposed on the primary side and obtain the residual amount of harmonic current after mutual cancellation. The compensation module 603 is used to extract higher harmonic components based on characteristic harmonic amplitude data and residual harmonic current through an active harmonic compensation unit integrated in the transformer, and inject a first compensation current with equal amplitude and opposite phase to the higher harmonic components into the common node of the transformer winding.

[0049] Figure 7 This is a schematic diagram illustrating the application of a transformer for AI computing power supply and energy storage equipment in an embodiment of the present invention. The GPU server cluster consists of multiple GPU servers connected in parallel. Each GPU server is equipped with a switching power supply ×N. When operating in parallel, it continuously injects characteristic harmonic current into the primary side of the transformer. The transformer includes: a primary winding, a multi-split phase-shifting winding, an active harmonic compensation unit, a common node for the transformer winding, and a collaborative control unit. The primary winding receives harmonic currents injected by the GPU server cluster and performs current spectrum analysis. The multi-splitting phase-shifting winding passively cancels low-order characteristic harmonic currents by introducing inter-winding phase angle differences and employing differentiated turns ratios. The residual harmonic current after cancellation is transmitted to the active harmonic compensation unit via a dashed arrow. The active harmonic compensation unit extracts the 17th and higher-order harmonic components and, after coupling through the injection transformer, injects a compensation current with equal amplitude and opposite phase to the higher-order harmonic components into the common node of the transformer windings. The common node of the transformer windings is the point where the passive cancellation output and the active compensation current converge. The collaborative control unit dynamically coordinates the multi-splitting phase-shifting winding and the active harmonic compensation unit based on the total distortion rate of the primary harmonic current of the transformer, maintaining the total distortion rate of the harmonic current within a set limit. After the above-mentioned layered harmonic suppression processing, the harmonic voltage distortion rate on the DC bus is reduced, ensuring the conversion efficiency of the GPU power module.

[0050] In this embodiment, the specific implementation of each unit in the above device embodiment is described in the above method embodiment, and will not be repeated here.

[0051] It should be noted that, in this document, the terms "comprising," "including," or any other variations thereof are intended to cover non-exclusive inclusion, such that a process, apparatus, article, or method that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such process, apparatus, article, or method. Unless otherwise specified, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, apparatus, article, or method that includes that element.

[0052] The above description is only a preferred embodiment of the present invention and does not limit the patent scope of the present invention. Any equivalent structural or procedural transformations made based on the content of the present invention specification and drawings, or direct or indirect applications in other related technical fields, are similarly included within the patent protection scope of the present invention.

Claims

1. A harmonic suppression method for a transformer used in AI computing power energy storage equipment, characterized in that, include: Obtain the current on the primary side of the transformer and calculate the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. Based on the phase angle difference parameter, the phase angle difference between windings is introduced into each split winding and the turns ratio is arranged so that the low-order characteristic harmonic currents cancel each other out when the split windings are superimposed on the primary side and the residual amount of harmonic current after mutual cancellation is obtained. Based on the characteristic harmonic amplitude data and the residual harmonic current, the higher harmonic components are extracted by the active harmonic compensation unit integrated in the transformer, and a first compensation current with the same amplitude and opposite phase to the higher harmonic components is injected into the common node of the transformer winding.

2. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 1, characterized in that, After injecting a first compensation current of equal amplitude and opposite phase to the higher harmonic components into the common node of the transformer windings, the process further includes: Calculate the total harmonic current distortion rate on the primary side of the transformer; When the total harmonic distortion rate does not exceed the set limit, the passive cancellation state of each split winding is maintained and the active harmonic compensation unit is kept in the first compensation bandwidth. When the total harmonic current distortion rate exceeds the set limit, the split windings and the active harmonic compensation unit are adjusted in coordination until the total harmonic current distortion rate drops below the set limit.

3. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 2, characterized in that, When the total harmonic current distortion rate exceeds a set limit, the split windings and the active harmonic compensation unit are coordinated and adjusted until the total harmonic current distortion rate drops below the set limit, including: When the total distortion rate of the harmonic current exceeds the set limit, the set of excessive harmonic orders is obtained; Based on the set of out-of-standard harmonic orders, the lower edge of the second compensation bandwidth of the active harmonic compensation unit is extended to the frequency corresponding to the lowest harmonic order in the set of out-of-standard harmonic orders, and an extended compensation current command covering the set of out-of-standard harmonic orders is generated. The extended compensation current command is input into the PWM inverter for modulation, and a second compensation current is injected into the common node of the transformer winding through the injection transformer until the total distortion rate of the harmonic current drops to within the set limit, and the active harmonic compensation unit is restored to the standard compensation bandwidth.

4. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 1, characterized in that, The process of acquiring the primary current of the transformer and calculating the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings during parallel operation of the GPU server switching power supply includes: The current on the primary side of the transformer is obtained, and a discrete Fourier transform is performed on the current on the primary side of the transformer to obtain the characteristic harmonic amplitude data of the 5th, 7th, 11th, 13th, 17th and 19th harmonics. Based on the characteristic harmonic amplitude data, the target harmonic order that needs to be passively canceled is determined and the phase angle difference parameters of each split winding are derived.

5. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 4, characterized in that, The process of determining the target harmonic order to be passively canceled and deriving the phase angle difference parameters of each split winding based on the characteristic harmonic amplitude data includes: Calculate the proportion of each harmonic amplitude to the fundamental amplitude in the characteristic harmonic amplitude data, and determine the harmonic number whose proportion exceeds the proportion threshold as the target harmonic number; Substituting the target harmonic number into the cancellation condition that the product of each target harmonic number and the phase angle difference is equal to an odd multiple of 180°, the phase angle difference parameters of each split winding are obtained.

6. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 1, characterized in that, The step of introducing inter-winding phase angle differences and arranging turns ratios for each split winding based on the phase angle difference parameter, so that the low-order characteristic harmonic currents cancel each other out when superimposed on the primary side of each split winding, and obtaining the residual amount of harmonic current after mutual cancellation, includes: Based on the phase angle difference parameter, a phase angle difference between windings is introduced for each split winding, so that the low-order characteristic harmonic currents cancel each other out when the split windings are superimposed on the primary side. The low-order characteristic harmonic currents are characteristic harmonic currents of the 5th to 13th order. Based on the relative deviation of the amplitude of the low-order characteristic harmonic current in each split winding relative to the corresponding target harmonic current reference amplitude, the equivalent turns ratio correction ratio of each split winding referred to the primary side is calculated; and within the allowable turns ratio deviation range of the split winding, the turns ratio correction amount of each split winding is determined. The turns ratio of each split winding is arranged according to the turns ratio correction amount, and the residual harmonic current after mutual cancellation is obtained.

7. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 6, characterized in that, The step of arranging the turns ratios of each split winding according to the turns ratio correction amount and obtaining the residual harmonic current after mutual cancellation includes: The rated turns ratio of each split winding is added together with the turns ratio correction amount to obtain the actual turns ratio of each split winding; Based on the actual turns ratio, the low-order characteristic harmonic currents in each split winding are converted to the primary side according to the actual turns ratio and then vector superimposed to obtain the residual harmonic current after the low-order characteristic harmonic currents cancel each other out.

8. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 1, characterized in that, The step of extracting higher-order harmonic components based on the characteristic harmonic amplitude data and the residual harmonic current, through an active harmonic compensation unit integrated within the transformer, and injecting a first compensation current with equal amplitude but opposite phase to the higher-order harmonic components into the common node of the transformer windings, includes: Obtain the compensation priority and compensation amplitude constraints corresponding to the residual harmonic current, and perform Clarke transformation on the three-phase current of the primary side of the transformer to obtain the two-phase current components in the stationary coordinate system. A low-pass filter with a cutoff frequency lower than the 5th harmonic frequency is applied to the two-phase current components to separate the fundamental component; after subtracting the two-phase current components from the fundamental component, a bandpass filter covering the 17th to 19th harmonic frequency range is applied to extract the 17th and 19th higher harmonic components. Based on the higher harmonic components and the current conversion relationship of the injected transformer, a compensation current command that is inversely related to the higher harmonic components at the common node of the transformer winding is generated, and the first compensation current is output through the PWM inverter in the active harmonic compensation unit and coupled to the common node of the transformer winding via the injected transformer.

9. The harmonic suppression method for a transformer used in AI computing power energy storage equipment according to claim 8, characterized in that, The process involves generating a compensation current command that is inversely related to the higher harmonic components at the common node of the transformer windings, based on the current conversion relationship between the higher harmonic components and the injected transformer. This compensation current is then output through the PWM inverter in the active harmonic compensation unit and coupled to the common node of the transformer windings via the injected transformer. The process includes: Based on the higher harmonic components, a proportional resonant controller with the corresponding harmonic frequency as the resonant frequency is configured for each higher harmonic frequency; the proportional resonant controller performs frequency selective tracking of the higher harmonic components, and combines the phase compensation parameters, the injection transformer conversion factor and the PWM inverter current limit to obtain a compensation current command that is opposite to the corresponding higher harmonic component at the common node of the transformer winding. The compensation current command is input to the PWM inverter in the active harmonic compensation unit integrated in the transformer for modulation to obtain the first compensation current, which is then injected into the common node of the transformer winding after being coupled through the transformer.

10. A harmonic suppression device for a transformer used in an AI computing power energy storage device, characterized in that, The steps for implementing the harmonic suppression method for a transformer used in an AI computing power energy storage device according to any one of claims 1 to 9 include: The calculation module is used to obtain the current on the primary side of the transformer and calculate the characteristic harmonic amplitude data injected into the primary side of the transformer and the phase angle difference parameters of the multi-split windings when the GPU server switching power supply is running in parallel. The mutual cancellation module is used to introduce the inter-winding phase angle difference for each split winding and arrange the turns ratio based on the phase angle difference parameter, so that the low-order characteristic harmonic currents cancel each other when the split windings are superimposed on the primary side and obtain the residual amount of harmonic current after mutual cancellation. The compensation module is used to extract higher harmonic components based on the characteristic harmonic amplitude data and the residual harmonic current, through an active harmonic compensation unit integrated in the transformer, and inject a first compensation current with the same amplitude and opposite phase to the higher harmonic components into the common node of the transformer winding.

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