Electronic device

Abstract

The application discloses an electronic device, and belongs to the technical field of electronic devices. The electronic device comprises an electronic device main body, a main radiation unit, a parasitic radiation unit and a grounding inductive element. The main radiation unit has a first feeding connection end, and the main radiation unit extends along the side edge of the electronic device main body. The parasitic radiation unit comprises a first parasitic branch, a second parasitic branch and a connection node. The first parasitic branch is coupled to one end of the main radiation unit away from the first feeding connection end, and the first parasitic branch and the second parasitic branch meet at the connection node. The grounding inductive element is connected between the connection node and a reference ground. The first parasitic branch extends along the side edge of the electronic device main body, and at least part of the second parasitic branch extends along the bottom edge of the electronic device main body. The grounding inductive element is used for cooperating with the parasitic radiation unit to stimulate a common mode resonance mode.

Description

Technical Field

[0001] This application belongs to the field of electronic equipment technology, and specifically relates to an electronic device. Background Technology

[0002] As mobile devices continue to evolve towards thinner and lighter designs, internal assembly space becomes increasingly limited, leading to the widespread adoption of unidirectional radiator layouts for conventional antennas. This unidirectional radiator layout results in a highly concentrated near-field energy distribution. When a user holds the mobile device or uses it close to their body, this concentrated near-field energy is easily coupled and absorbed by human tissue. To meet electromagnetic safety standards, mobile devices often implement transmit power limitations, which degrades antenna communication performance. However, maintaining normal transmit power to ensure stable communication exacerbates radiation absorption by the human body, creating an irreconcilable conflict between stable antenna communication output and radiation safety control. Summary of the Invention

[0003] The purpose of this application is to provide an electronic device that can stabilize antenna communication performance, optimize antenna near-field energy distribution, reduce electromagnetic absorption by the human body, improve communication attenuation caused by power limitation, and balance communication needs with electromagnetic radiation safety.

[0004] In a first aspect, embodiments of this application provide an electronic device, including: an electronic device body, a main radiating unit, a parasitic radiating unit, and a grounding inductor; the main radiating unit has a first feed connection terminal and extends along the side of the electronic device body; the parasitic radiating unit includes a first parasitic branch, a second parasitic branch, and a connection node, the first parasitic branch is coupled to the end of the main radiating unit away from the first feed connection terminal, and the first parasitic branch and the second parasitic branch intersect at the connection node; the grounding inductor is connected between the connection node and a reference ground; wherein, the first parasitic branch extends along the side of the electronic device body, and at least a portion of the second parasitic branch extends along the bottom edge of the electronic device body; the grounding inductor is used to cooperate with the parasitic radiating unit to excite the formation of a common-mode resonant mode.

[0005] In this embodiment, the electronic device includes: an electronic device body, a main radiating unit, a parasitic radiating unit, and a grounding inductor. The main radiating unit receives signals through a first feed connection terminal and undertakes the excitation and main radiation functions of the electronic device. The first parasitic branch obtains excitation from the main radiating unit through coupling induction and generates an induced current, enabling the parasitic radiating unit to cooperate with the main radiating unit to complete the radiation work. The grounding inductor provides a controllable grounding path for the current at the connection node, realizing precise tuning of the resonant state and impedance matching performance of the parasitic radiating unit. The first parasitic branch extends along the side of the electronic device body, and at least part of the second parasitic branch extends along the bottom edge of the electronic device body, forming a corner double-direction layout. The grounding inductor cooperates with the parasitic radiating unit to excite and form a common-mode resonant mode. In the common-mode resonant mode, the currents of the main radiating unit and the parasitic radiating unit have a specific phase relationship, generating an opposing electromagnetic field to cancel the strong near-field radiation on the side of the electronic device, while guiding the electromagnetic energy to the low-sensitivity area at the bottom edge of the electronic device, reducing energy accumulation in the side area. Based on the above structure, the specific absorption rate of electronic devices in close-contact scenarios can be significantly reduced, while mitigating the decrease in radiation efficiency when held by the hand, thus greatly improving electromagnetic safety characteristics while ensuring stable communication performance. Attached Figure Description

[0006] Figure 1 This is a schematic diagram of the structure of an electronic device provided in an embodiment of this application;

[0007] Figure 2 A one-dimensional simulation efficiency curve of the electronic device provided in the embodiments of this application;

[0008] Figure 3 An S-parameter impedance view of an electronic device provided in an embodiment of this application;

[0009] Figure 4 A schematic diagram of the current distribution of the electronic device provided in the embodiment of this application under the same current distribution mode;

[0010] Figure 5 A schematic diagram of the current distribution of an electronic device in 0° phase common-mode resonance mode provided in an embodiment of this application;

[0011] Figure 6 A schematic diagram of the current distribution of an electronic device in 90° phase common-mode resonance mode, provided in an embodiment of this application;

[0012] Figure 7 A schematic diagram of the current distribution of an electronic device in differential mode provided in an embodiment of this application;

[0013] Figure 8 This is a schematic diagram of the structure of another electronic device provided in an embodiment of this application.

[0014] Reference numerals: 10, electronic device; 20, main body of electronic device; 21, side; 22, bottom; 30, circuit board; 40, reference ground; 100, main radiating unit; 101, first feed connection terminal; 200, parasitic radiating unit; 210, first parasitic branch; 220, second parasitic branch; 230, connection node; 300, grounding inductor; 222, first part; 224, second part; 400, coupling capacitor; 401, lumped capacitor; 402, metal structure; 500, first switch; 600, second switch; 700, auxiliary radiating unit; 701, second feed connection terminal; 702, grounding terminal; 703, coupling terminal. Detailed Implementation

[0015] The technical solutions of the embodiments of this application will be clearly described below with reference to the accompanying drawings. Obviously, the described embodiments are only some, not all, of the embodiments of this application. All other embodiments obtained by those skilled in the art based on the embodiments of this application are within the scope of protection of this application.

[0016] The terms "first," "second," etc., used in the specification and claims of this application are used to distinguish similar objects and not to describe a specific order or sequence. It should be understood that such use of data can be interchanged where appropriate so that embodiments of this application can be implemented in orders other than those illustrated or described herein, and the objects distinguished by "first," "second," etc., are generally of the same class and the number of objects is not limited; for example, a first object can be one or more. Furthermore, in the specification and claims, "and / or" indicates at least one of the connected objects, and the character " / " generally indicates that the preceding and following objects are in an "or" relationship.

[0017] The electronic device provided in the embodiments of this application will be described in detail below with reference to the accompanying drawings and through specific embodiments and application scenarios.

[0018] like Figure 1As shown, this application embodiment provides an electronic device 10, including: an electronic device body 20, a main radiating unit 100, a parasitic radiating unit 200, and a grounding inductor 300; the main radiating unit 100 has a first feed connection terminal 101, and the main radiating unit 100 extends along the side 21 of the electronic device body 20; the parasitic radiating unit 200 includes a first parasitic branch 210, a second parasitic branch 220, and a connection node 230, the first parasitic branch 210 is coupled to the end of the main radiating unit 100 away from the first feed connection terminal 101, and the first parasitic branch 210 and the second parasitic branch 220 intersect at the connection node 230; the grounding inductor 300 is connected between the connection node 230 and a reference ground 40; wherein, the first parasitic branch 210 extends along the side 21 of the electronic device body 20, and at least a portion of the second parasitic branch 220 extends along the bottom edge 22 of the electronic device body 20; the grounding inductor 300 is used to cooperate with the parasitic radiating unit 200 to excite the formation of a common-mode resonant mode.

[0019] In the above embodiments, the electronic device 10 includes: an electronic device body 20, a main radiating unit 100, a parasitic radiating unit 200, and a grounding inductor 300. The main radiating unit 100 receives signals through a first feed connection terminal 101 and undertakes the core excitation and main radiation functions of the electronic device 10. The first parasitic branch 210 obtains excitation from the main radiating unit 100 through coupling induction and generates an induced current, enabling the parasitic radiating unit 200 to cooperate with the main radiating unit 100 to complete the radiation work. The grounding inductor 300 provides a controllable grounding path for the current at the connection node 230, realizing precise tuning of the resonant state and impedance matching performance of the parasitic radiating unit 200. The first parasitic branch 210 extends along the side 21 of the main body 20 of the electronic device, and at least part of the second parasitic branch 220 extends along the bottom edge 22 of the main body 20 of the electronic device, forming a corner-oriented dual-direction layout. The grounding inductor element cooperates with the parasitic radiation unit to excite the formation of a common-mode resonant mode. In the common-mode resonant mode, the currents of the main radiation unit and the parasitic radiation unit have a specific phase relationship, generating an opposing electromagnetic field to cancel the strong near-field radiation on the side of the electronic device, while guiding the electromagnetic energy to the low-sensitivity area at the bottom edge of the electronic device, reducing energy accumulation in the side area. Based on the above structure, the specific absorption rate of the electronic device 10 in close-fitting scenarios can be significantly reduced, while mitigating the decrease in radiation efficiency when held by a human hand, thus greatly improving electromagnetic safety characteristics while ensuring stable communication performance.

[0020] Understandably, the corner dual-direction layout is used to transfer radiated energy from the high-risk side area to the low-risk bottom area in order to reduce specific absorption rate; in a 0mm close-fitting scenario, the aforementioned electronic device 10 can achieve a derating performance improvement of about 3dB.

[0021] For example, such as Figure 1As shown, the electronic device 10 includes a circuit board 30, and a first power supply connection terminal 101 is connected to the circuit board 30.

[0022] For example, such as Figure 2 As shown, Figure 2 The horizontal axis represents frequency in gigahertz (GHz), and the vertical axis represents the corresponding amplitude in decibels (dB). The upper curve represents the radiation efficiency of a monopole + T-type antenna (Rad. Efficiencymonopole+T); the lower curve represents the system total efficiency of a monopole + T-type antenna (System Total. Efficiencymonopole+T). CM represents the common-mode resonant mode; DM represents the differential-mode resonant mode. This curve shows that through the design of electronic equipment, two resonant modes can be excited within the target operating frequency band, with the common-mode resonant mode being the core operating state for the antenna to achieve low specific absorption characteristics.

[0023] For example, the side 21 of the main body 20 of the electronic device can be either the left side or the right side.

[0024] For example, such as Figure 3 The figure shows the S-parameter impedance view (Smith chart) of the electronic device 10 provided in the embodiment of this application, which shows the impedance distribution of the electronic device 10 at 0.7 GHz, 0.8 GHz, 0.9 GHz and 1.0 GHz. CM corresponds to the impedance region of the common-mode resonant mode and DM corresponds to the impedance region of the differential-mode resonant mode. This shows that the electronic device 10 can excite stable common-mode resonance and differential-mode resonance in the target frequency band, and realize dual-mode impedance matching and resonance control.

[0025] For example, at operating frequencies of approximately 0.8 GHz and below, electronic device 10 operates in a current-unidirectional distribution mode. Figure 4 As shown, at this time, the current is mainly concentrated in the main radiating unit 100 and the first parasitic branch 210, and the current direction is consistent. The electronic device 10 as a whole presents the current distribution pattern of a monopole antenna paired with a parasitic radiating unit 200.

[0026] For example, at an operating frequency of approximately 0.9 GHz, the electronic device 10 operates in common-mode resonant mode. As... Figure 5 and Figure 6 As shown, at this time, the grounding inductor 300 and the parasitic radiation unit 200 cooperate to generate a high-intensity common-mode current. During a portion of the signal cycle, the current direction of the main radiation unit 100 and the first parasitic branch 210 is opposite. By using the reverse electromagnetic field to cancel the near-field radiation on the side of the device, the main radiated energy is guided to the bottom region of the device, achieving the lowest specific absorptivity and excellent anti-holding attenuation performance. The common-mode resonant mode is the core operating state for achieving the low specific absorptivity effect in the embodiments of this application.

[0027] For example, at an operating frequency of approximately 1.0 GHz, the electronic device 10 operates in differential-mode resonant mode. As... Figure 7 As shown, at this time, the parasitic radiation unit 200 internally generates a differential-mode current, and the overall current of the electronic device 10 is uniformly distributed in the same direction. The specific absorption rate under this operating state is lower than that of the current-uniform distribution mode, and since there is no obvious reverse current cancellation mechanism, its specific absorption rate is higher than that of the common-mode resonant mode.

[0028] For example, Figure 4 , Figure 5 , Figure 6 and Figure 7 The arrows in the diagram indicate the direction of the current in the corresponding region.

[0029] The performance comparison data of the embodiments of this application and the control scheme are shown in Table 1.

[0030] Table 1. Performance comparison data between the embodiments of this application and the comparative scheme.

[0031]

[0032] The table shows the test results for the control scheme (monopole + 1 / 4 parasitic), which is a monopole antenna electronic device using a traditional 1 / 4 wavelength parasitic branch, a common optimization scheme for low-frequency antennas in related technologies. The table below shows the test results for the embodiment of this application (monopole + T). In the table, frequency (GHz) is the antenna's operating center frequency; radFS efficiency is the free-space radiation efficiency; 0mmright efficiency is the antenna efficiency in a close-to-human-human scenario; 23dBmSAR is the specific absorptivity at a transmit power of 23dBm; 10gFS-5 normalized is the normalized SAR (Specific Absorption Rate) index based on 10g of human tissue; normalized TRP is the normalized total radiated power; the "gap" column represents the efficiency improvement difference between the embodiment of this application and the control scheme, with negative values ​​representing the efficiency improvement.

[0033] The data comparison shows that the embodiments of this application achieve a significant reduction in SAR (Specific Absorption Rate) and an improvement in radiation efficiency within the target operating frequency band. In the 0.9 GHz common-mode resonant mode, the SAR value decreased from 2.78 in the control scheme to 1.14, a reduction of over 59%. Simultaneously, the efficiency in the 0mm close-range scenario improved from -15.33 to -5.5, an improvement of nearly 10 dB, and the normalized TRP increased from 16.54 to 19.78, verifying the dual optimization effect of low SAR and high efficiency. At 0.8 GHz and 1.0 GHz, the SAR values ​​of the embodiments of this application are also lower than the control scheme, and both the efficiency and normalized TRP in the close-range scenario are improved, proving that this scheme has good low SAR and anti-human-obstruction performance across the entire target frequency band.

[0034] For example, the electronic device 10 can be applied to mobile electronic devices such as mobile phones, tablets, and watches.

[0035] like Figure 1 As shown, in some embodiments of this application, the second parasitic branch 220 includes a first part 222 and a second part 224 connected to each other. The first part 222 is connected to the connection node 230 and extends along the side 21 of the electronic device body 20; the second part 224 extends along the bottom edge 22 of the electronic device body 20.

[0036] In the above embodiments, the second parasitic branch 220 regulates the current conduction direction through segmented arrangement with different orientations, reasonably diverts the radiated current, clarifies the current transmission path, strengthens the excitation effect of common-mode resonance, stabilizes the common-mode operating state, optimizes the near-field energy distribution of the antenna, reduces the specific absorption rate, and weakens the performance impact of human body obstruction on the electronic device 10.

[0037] For example, the first part 222 and the second part 224 are arranged perpendicular to each other.

[0038] For example, the first part 222 and the second part 224 adopt an integral structure.

[0039] In some embodiments of this application, the length of the first portion 222 of the second parasitic branch 220 is less than one-third of the sum of the lengths of the first parasitic branch 210 and the second parasitic branch 220.

[0040] In the above embodiments, the length of the first part 222 of the second parasitic branch 220 is less than one-third of the sum of the lengths of the first parasitic branch 210 and the second parasitic branch 220, which can guide the current to stably shunt from the side region to the bottom region, balance the energy distribution between the side region and the bottom region, strengthen the common-mode excitation effect, avoid excessive current concentration in the side region, further optimize the near-field radiation distribution, and improve the low specific absorption rate performance of the electronic device 10.

[0041] It can be understood that, as Figure 1 shown, Figure 1 in which L2 is used to represent the sum of the lengths of the first parasitic branch 210 and the first part 222 of the second parasitic branch 220; D1 is used to represent the length of the first part 222 of the second parasitic branch 220; L3 is used to represent the length of the second part 224 of the second parasitic branch 220. That is, the first parasitic branch 210 and the second parasitic branch 220 should satisfy: D1 < 1 / 3 (L2 + L3).

[0042] Exemplarily, the length of the first part 222 of the second parasitic branch 220 can be set to one-fifth of the length of the first parasitic branch 210.

[0043] In some embodiments of the present application, the sum of the lengths of the first parasitic branch 210 and the first part 222 of the second parasitic branch 220 is greater than two-thirds of the second part 224 of the second parasitic branch 220 and less than four-thirds of the second part 224 of the second parasitic branch 220.

[0044] In the above embodiments, the sum of the lengths of the first parasitic branch 210 and the first part 222 of the second parasitic branch 220 is greater than two-thirds of the second part 224 of the second parasitic branch 220 and less than four-thirds of the second part 224 of the second parasitic branch 220, so as to form a matching and coordinated resonance relationship between the side extension branch and the bottom extension branch, ensure the full excitation of the common-mode, enable the electronic device 10 to maintain a lower specific absorption rate and a more stable radiation efficiency within the target operating frequency band, narrow the excitation intensity between the side branch and the bottom branch, and ensure the balance and stability of the resonance effect.

[0045] It can be understood that, as Figure 1 shown, the first parasitic branch 210 and the second parasitic branch 220 should satisfy: 2 / 3 < L2 / L3 < 4 / 3. Exemplarily, the sum of the lengths of the first parasitic branch 210 and the first part 222 of the second parasitic branch 220 is equal to the length of the second part 224 of the second parasitic branch 220.

[0046] Exemplarily, the sum of the length of the first parasitic branch 210 and the length of the first part 222 of the second parasitic branch 220 is ten-elevenths of the length of the second part 224 of the second parasitic branch 220.

[0047] In some embodiments of the present application, the main radiation unit 100 extends along the side 21 of the electronic device body 20; taking the wavelength corresponding to the center frequency of the operating frequency band of the electronic device 10 as the reference wavelength, the length of the main radiation unit 100 is greater than one-quarter of the reference wavelength and less than one-half of the reference wavelength.

[0048] In the above embodiment, the main radiation unit 100 extends along the side 21 of the electronic device body 20. Taking the wavelength corresponding to the center frequency of the operating frequency band of the electronic device 10 as the reference wavelength, the length of the main radiation unit 100 is greater than one-quarter of the reference wavelength and less than one-half of the reference wavelength, so that the main radiation unit 100 forms a stable monopole radiation pattern in the target frequency band, ensuring the intensity of the basic radiation signal and the impedance matching state, and providing a stable energy source for the main radiation unit 100 to transfer the coupling excitation to the parasitic radiation unit 200, which can ensure that the main radiation unit 100 forms an effective radiation in the target low-frequency band.

[0049] It can be understood that, as Figure 1 shown, Figure 1 L1 in it is used to represent the length of the main radiation unit 100; the length of the main radiation unit 100 should satisfy: 1 / 4λ < L1 < 1 / 2λ; where, λ is used to represent the reference wavelength.

[0050] In some embodiments of the present application, taking the wavelength corresponding to the center frequency of the operating frequency band of the electronic device 10 as the reference wavelength, the sum of the length of the first parasitic branch 210 and the length of the first part 222 of the second parasitic branch 220 is greater than one-eighth of the reference wavelength and less than three-eighths of the reference wavelength; the length of the second part 224 of the second parasitic branch 220 is greater than one-eighth of the reference wavelength and less than three-eighths of the reference wavelength.

[0051] In the above embodiment, taking the wavelength corresponding to the center frequency of the operating frequency band of the electronic device 10 as the reference wavelength, the sum of the length of the first parasitic branch 210 and the length of the first part 222 of the second parasitic branch 220 is greater than one-eighth of the reference wavelength and less than three-eighths of the reference wavelength, and the length of the second part 224 of the second parasitic branch 220 is greater than one-eighth of the reference wavelength and less than three-eighths of the reference wavelength, ensuring that the parasitic radiation unit 200 obtains a suitable excitation intensity and an accurate resonance frequency point in the target low-frequency operating frequency band, maintaining the stable operation of the common-mode and differential-mode, making the electronic device 10 maintain the characteristics of low specific absorption rate and high radiation efficiency in the target frequency band, and ensuring that the parasitic radiation unit 200 excites a stable common-mode resonance in the target frequency band.

[0052] It can be understood that, as Figure 1 shown, the length of the first parasitic branch 210 and the length of the second parasitic branch 220 should satisfy: 1 / 8λ < L2 < 3 / 8λ and 1 / 8λ < L3 < 3 / 8λ; where λ is used to represent the reference wavelength.

[0053] Exemplarily, the sum of the lengths of the first parasitic branch 210 and the first part 222 of the second parasitic branch 220 is one quarter of the reference wavelength.

[0054] Exemplarily, the length of the second part 224 of the second parasitic branch 220 is one quarter of the reference wavelength.

[0055] In some embodiments of the present application, the second parasitic branch 220 extends along the bottom edge 22 of the electronic device body 20 as a whole, and the length of the first parasitic branch 210 is equal to the length of the second parasitic branch 220.

[0056] In the above embodiment, the second parasitic branch 220 extends along the bottom edge 22 of the electronic device body 20 as a whole, and the length of the first parasitic branch 210 is equal to the length of the second parasitic branch 220, so that the parasitic radiation unit 200 forms a symmetric layout structure, balances the current distribution, strengthens the common-mode resonance excitation effect, and makes the specific absorption rate optimization effect of the electronic device 10 reach the optimal state. The symmetric branch layout can maximize the design advantage of low specific absorption rate.

[0057] It can be understood that if the second parasitic branch 220 extends along the bottom edge 22 of the electronic device body 20 as a whole, there is no first part, that is, D1 is equal to zero. Exemplarily, the first parasitic branch 210 and the second parasitic branch 220 are arranged perpendicular to each other, and the connection node 230 is directly located at the corner position of the electronic device body 20.

[0058] Exemplarily, the first parasitic branch 210 and the second parasitic branch 2 are located in the same corner area of the electronic device body 0.

[0059] As Figure 1 shown, in some embodiments of the present application, the electronic device 10 further includes a coupling capacitor 400, and the first parasitic branch 210 is coupled to the main radiation unit 100 through the coupling capacitor 400.

[0060] In the above embodiment, the coupling capacitor 400 enhances the coupling strength between the main radiation unit 100 and the first parasitic branch 210, improves the excitation efficiency of the main radiation unit 100 for the parasitic radiation unit 200, stabilizes the common-mode working mode, improves the overall input impedance matching performance of the electronic device 10, expands the working bandwidth of the electronic device 10, and can flexibly adjust the excitation intensity between branches by means of the coupling capacitor 400 to ensure the continuous and stable excitation of the common-mode mode.

[0061] For example, the coupling capacitor 400 is disposed at the gap position between the main radiating unit 100 and the first parasitic branch 210.

[0062] For example, the coupling capacitor 400 is connected to the main radiating unit 100 and the first parasitic branch 210 through a spring or conductive structure.

[0063] like Figure 1 and Figure 8 As shown, in some embodiments of this application, the coupling capacitor 400 is a lumped capacitor 401; or the coupling capacitor 400 is a metal structure 402, which is disposed between the main radiating unit 100 and the first parasitic branch 210, and the metal structure 402 has a gap to form capacitive coupling between the main radiating unit 100 and the first parasitic branch 210.

[0064] In the above embodiments, the coupling capacitor 400 can be a lumped capacitor 401 for precise control; alternatively, the coupling capacitor 400 can be a metal structure 402. The metal structure 402 is positioned between the main radiating unit 100 and the first parasitic branch 210, and the gaps on the metal structure 402 form an equivalent capacitor structure, thereby achieving low-cost integration. Both implementations ensure a stable coupling excitation relationship between the main radiating unit 100 and the first parasitic branch 210, thus exciting the parasitic radiating unit 200. These two implementations can flexibly adapt to different overall layout requirements, improving manufacturability and design flexibility, reducing assembly costs, and saving internal space.

[0065] For example, such as Figure 8 As shown, the metal structure 402 can be a section of flexible printed circuit board. By etching a gap in the flexible printed circuit board, the gap is used to form an equivalent capacitor, thereby realizing the required capacitive coupling function between the main radiating unit 100 and the first parasitic branch 210. This solution is low in cost, flexible in processing, easy to integrate, and can save space.

[0066] In some embodiments of this application, the capacitance value of the coupling capacitor 400 ranges from 0.3 picofarads to 1.5 picofarads.

[0067] In the above embodiments, the capacitance value of the coupling capacitor 400 is in the range of 0.3 picofarads to 1.5 picofarads, ensuring that the excitation intensity between the main radiating unit 100 and the parasitic radiating unit 200 is within a reasonable range, avoiding the decrease in radiation efficiency caused by insufficient excitation or the bandwidth contraction caused by excessive excitation, maintaining the good radiation efficiency and low specific absorption rate characteristics of the electronic device 10 in the target frequency band, and simultaneously taking into account the coupling excitation intensity and the antenna operating bandwidth.

[0068] For example, the capacitance value of coupling capacitor 400 is 0.5 picofarads or 1 picofarad.

[0069] In some embodiments of this application, the grounding inductor 300 is a lumped inductor; or the grounding inductor 300 is a bent metal continuous structure.

[0070] In the above embodiments, the grounding inductor 300 adopts a lumped inductor device to achieve precise parameter control, or adopts a bent metal continuous structure to achieve compact layout. Both implementations can provide a stable and controllable inductive grounding path for the connection node 230, ensuring the reliable execution of the grounding tuning function. Discrete devices or metal forming structures can be selected to complete the inductive grounding design according to the overall space.

[0071] In some embodiments of this application, the metal connecting structure is arranged in a Z-shape and there is an insulating gap between it and the surrounding metal components.

[0072] In the above embodiments, the metal connecting structure is arranged in a Z-shape. The insulation gap can prevent parasitic coupling between the metal connecting structure and the surrounding metal components, stabilize the equivalent inductance value of the metal connecting structure, ensure the consistency and reliability of the grounding tuning effect, and reserve a safe distance to avoid interference from surrounding metal components and ensure the stability of inductance parameters.

[0073] For example, the insulation gap is greater than 0.6 mm.

[0074] In some embodiments of this application, the inductance of the grounding inductor 300 ranges from 0.5 nanohenries to 3 nanohenries.

[0075] In the above embodiments, the inductance of the grounding inductor 300 ranges from 0.5 nanohenries to 3 nanohenries, ensuring that the common-mode resonant frequency of the parasitic radiation unit 200 is stably located near the target low-frequency operating band, maintaining the electronic device 10 in the optimal low specific absorption rate and high radiation efficiency operating state within the operating frequency band, and accurately adjusting and matching the common-mode resonance to the target communication frequency band.

[0076] For example, the inductance value of the grounding inductor 300 is 0.5 nanohenries or the inductance value of the grounding inductor 300 is 1 nanohenry.

[0077] like Figure 8 As shown, in some embodiments of this application, the electronic device 10 further includes: a first switch 500 disposed on the first parasitic branch 210; and a second switch 600 disposed on the second parasitic branch 220; wherein the first switch 500 and the second switch 600 are used to coordinately switch the common-mode resonant position of the parasitic radiation unit 200.

[0078] In the above embodiments, the first switch 500 and the second switch 600 dynamically adjust the effective electrical length of the parasitic radiation unit 200 by changing the current path of their respective branches, thereby adjusting the coordination relationship between the grounding inductor 300 and the parasitic radiation unit 200, changing the excitation conditions of common-mode resonance, and realizing the switching of the common-mode resonance position of the parasitic radiation unit 200. By switching the common-mode resonance position, the electronic device 10 can stably excite the common-mode resonance mode at different operating frequencies, continuously regulate the near-field energy distribution, reduce energy accumulation in the side regions, maintain a low specific absorption rate operating state, reduce the impact of human hand grip on radiation efficiency, and improve the communication performance consistency and electromagnetic safety characteristics of the electronic device 10 across the entire target frequency band.

[0079] Understandably, by adjusting the operating states of the first switch 500 and the second switch 600 according to the target operating frequency, the effective electrical length of the parasitic radiation unit 200 can be changed, so that the common-mode resonant position matches the target frequency. The first switch 500 and the second switch 600 can work individually or in combination, flexibly adapting to different frequency requirements, ensuring that the common-mode resonant mode can be stably excited within the target frequency band, and maintaining a low specific absorption rate operating state.

[0080] like Figure 8 As shown, in some embodiments of this application, the electronic device 10 further includes an auxiliary radiation unit 700, a ground terminal 702 and a coupling terminal 703, a second power supply connection terminal 701 located between the ground terminal 702 and the coupling terminal 703, the ground terminal 702 being connected to the reference ground 40, and the coupling terminal 703 being coupled to the end of the second parasitic branch 220 away from the first parasitic branch 210.

[0081] In the above embodiment, the auxiliary radiating unit 700 provides an additional radiation path for the electronic device 10; the second feed connection terminal 701 is used to receive the radio frequency excitation signal and realize signal feeding; the ground terminal 702 is connected to the reference ground 40 to provide a ground potential for the auxiliary radiating unit 700 and ensure stable resonance; the coupling terminal 703 realizes the coupling between the auxiliary radiating unit 700 and the second parasitic branch 220. The second feed connection terminal 701 is located between the ground terminal 702 and the coupling terminal 703 to form a stable radiation path; the coupling terminal 703 is coupled to the end of the second parasitic branch 220 away from the first parasitic branch 210, so that the auxiliary radiating unit 700 and the parasitic radiating unit 200 form an electromagnetic coupling relationship, expanding the operating frequency band of the electronic device 10 and covering the mid-to-high frequency radiation requirements.

[0082] For example, Figure 8 In this context, L4 is used to represent the length of the auxiliary radiating unit 700.

[0083] Table 2 shows the performance comparison data of the embodiments of this application after adding the medium- and high-frequency multiplexing branch and the switching function.

[0084] Table 2. Performance comparison data after adding medium- and high-frequency multiplexing sections and switching functions.

[0085]

[0086] The table shows the test results for the control scheme (monopole + 1 / 4 parasitic), which uses a traditional 1 / 4 wavelength parasitic stub monopole antenna structure, a common optimization scheme for low-frequency antennas. The table below shows the test results for the embodiment of this application (monopole + T) after introducing a mid-to-high frequency multiplexing stub and switching functionality. The "gap" column in the table represents the efficiency improvement difference between the embodiment of this application and the control scheme; negative values ​​represent the amount of efficiency improvement.

[0087] As can be seen from the data comparison, after introducing the mid-to-high frequency multiplexing branch and switching function, the embodiments of this application can still achieve stable low specific absorption rate (SAR) and low human body interference effects across the entire low-frequency band. Within the target frequency band of 0.7 GHz to 1 GHz, the SAR values ​​of the embodiments are significantly lower than the control scheme, with the SAR value at the 0.7 GHz frequency point decreasing from 2.17 to 1.10, a reduction of over 49%. Simultaneously, the efficiency improvement in 0mm close-range scenarios is significant, with normalized TRP remaining above 19 dB, verifying that the above scheme achieves low specific absorption rate while also maintaining excellent anti-human body interference performance. It should be noted that the data in Table 2 has been normalized to remove the influence of reflection coefficient and matching loss; the actual implementation effect may be slightly reduced, but the overall performance improvement trend remains unchanged.

[0088] In some embodiments of this application, the main radiating element 100 is a monopole antenna structure, and the first feed connection terminal 101 is connected to the radio frequency terminal of the motherboard of the electronic device 10.

[0089] In the above embodiment, the main radiating unit 100 is a monopole antenna structure. The first feed connection terminal 101 is directly connected to the RF terminal of the main board of the electronic device 10, omitting the coaxial feed line and antenna board structure, simplifying the overall composition of the electronic device 10, reducing assembly complexity and hardware cost, making full use of the side 21 of the electronic device 10, supporting the thin and light design of the electronic device 10, and the direct connection method can reduce intermediate transition components and improve the overall space utilization.

[0090] It should be noted that, in this document, the terms "comprising," "including," or any other variations thereof are intended to cover non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such a process, method, article, or apparatus. Without further limitations, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, method, article, or apparatus that includes that element. Furthermore, it should be noted that the scope of the methods and apparatuses in the embodiments of this application is not limited to performing functions in the order shown or discussed, but may also include performing functions substantially simultaneously or in the reverse order, depending on the functions involved. For example, the described methods may be performed in a different order than described, and various steps may be added, omitted, or combined. Additionally, features described with reference to certain examples may be combined in other examples.

[0091] The embodiments of this application have been described above with reference to the accompanying drawings. However, this application is not limited to the specific embodiments described above. The specific embodiments described above are merely illustrative and not restrictive. Those skilled in the art can make many other forms under the guidance of this application without departing from the spirit and scope of the claims, and all of these forms are within the protection scope of this application.

Claims

1. An electronic device, characterized in that, include: The main body of the electronic device; The main radiating unit has a first power supply connection terminal and extends along the side of the main body of the electronic device; The parasitic radiation unit includes a first parasitic branch, a second parasitic branch, and a connecting node. The first parasitic branch is coupled to the end of the main radiation unit away from the first feed connection end, and the first parasitic branch and the second parasitic branch intersect at the connecting node. A grounding inductor is connected between the connection node and the reference ground; The first parasitic branch extends along the side of the electronic device body, and at least a portion of the second parasitic branch extends along the bottom edge of the electronic device body; the grounding inductor element is used to cooperate with the parasitic radiation unit to excite the formation of a common-mode resonant mode.

2. The electronic device according to claim 1, characterized in that, The second parasitic branch includes a first part and a second part connected to each other. The first part is connected to the connection node and extends along the side of the electronic device body. The second part extends along the bottom of the electronic device body.

3. The electronic device according to claim 2, characterized in that, The length of the first part of the second parasitic branch is less than one-third of the sum of the lengths of the first parasitic branch and the second parasitic branch.

4. The electronic device according to claim 2, characterized in that, The sum of the length of the first parasitic branch and the length of the first part of the second parasitic branch is greater than two-thirds and less than four-thirds of the second part of the second parasitic branch.

5. The electronic device according to claim 2, characterized in that, The main radiating unit extends along the side of the electronic device body; with the wavelength corresponding to the center frequency of the electronic device's operating frequency band as the reference wavelength, the length of the main radiating unit is greater than one-quarter of the reference wavelength and less than one-half of the reference wavelength.

6. The electronic device according to claim 2, characterized in that, With the wavelength corresponding to the center frequency of the electronic device's operating frequency band as the reference wavelength, the sum of the length of the first parasitic branch and the length of the first part of the second parasitic branch is greater than one-eighth of the reference wavelength and less than three-eighths of the reference wavelength. The length of the second portion of the second parasitic branch is greater than one-eighth of the reference wavelength and less than three-eighths of the reference wavelength.

7. The electronic device according to claim 1, characterized in that, The second parasitic branch extends along the bottom edge of the main body of the electronic device, and the length of the first parasitic branch is equal to the length of the second parasitic branch.

8. The electronic device according to claim 1, characterized in that, Also includes: The first parasitic branch is coupled to the main radiating unit via a coupling capacitor.

9. The electronic device according to claim 8, characterized in that, The coupling capacitor is a lumped capacitor; or The coupling capacitor is a metal structure, which is located between the main radiating unit and the first parasitic branch, and the metal structure has a gap to form capacitive coupling between the main radiating unit and the first parasitic branch.

10. The electronic device according to claim 1, characterized in that, The grounding inductor is a lumped inductor; or the grounding inductor is a bent metal continuous structure.

11. The electronic device according to claim 10, characterized in that, The metal connecting structure is arranged in a Z-shape and has an insulating gap between it and the surrounding metal components.

12. The electronic device according to claim 1, characterized in that, Also includes: The first switch is located on the first parasitic branch; A second switch is located on the second parasitic branch; The first switch and the second switch are used to coordinately switch the common-mode resonant position of the parasitic radiation unit.

13. The electronic device according to claim 12, characterized in that, Also includes: The auxiliary radiating unit has a second feed connection terminal, a ground terminal, and a coupling terminal. The second feed connection terminal is located between the ground terminal and the coupling terminal. The ground terminal is connected to a reference ground. The coupling terminal is coupled to the end of the second parasitic branch that is away from the first parasitic branch.

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