Time division duplex mobile communication system

Abstract

The application discloses a time division duplex mobile communication system and belongs to the technical field of mobile communication. The system comprises an electrically scanned antenna, a radio frequency control device and a customer terminal device. The electrically scanned antenna comprises M antenna sectors. The radio frequency control device comprises a gating control circuit, a first directional coupler, a signal generation circuit and M transceiving circuits corresponding to the M antenna sectors. The gating control circuit is configured to monitor the signal quality of radio frequency signals on the M transceiving circuits and to select a target transceiving circuit from the M transceiving circuits to be connected to the customer terminal device according to the signal quality of the radio frequency signals on the M transceiving circuits. The first directional coupler is connected between the M transceiving circuits and the customer terminal device and is configured to extract a first radio frequency component from the transmission signals of the customer terminal device. The signal generation circuit is configured to generate a switch control signal according to the first radio frequency component to control the target transceiving circuit to switch between a transmission state and a receiving state. The application solves the technical problems of low transceiving isolation and long research and development cycle of the time division duplex mobile communication system.

Description

Technical Field

[0001] This invention belongs to the field of mobile communication technology, and particularly relates to a time-division duplex mobile communication system. Background Technology

[0002] In shipboard communication systems, 6-sector electronically scanned antennas offer fast beam pointing capabilities and high dynamic adaptability. The system consists of six independent antenna sectors, each containing several radiating elements to achieve beam tracking and signal coverage for the base station. In a shipboard environment, by monitoring the quality parameters of each sector in real time, the optimal antenna sector is dynamically selected to connect to the Customer Premise Equipment (CPE) for efficient data transmission. Time Division Duplex (TDD) signal processing is a crucial implementation method for mobile communication systems, its core feature being the time-division separation of transmission and reception through time slot allocation. However, the application of TDD-based mobile communication systems in shipboard environments faces significant challenges.

[0003] In related technologies, the transmit / receive isolation of TDD signal processing mainly relies on RF switches or circulators. RF switch solutions achieve time-division separation between the transmitting and receiving ends through physical switches; the normal operation of the RF switch depends on the precise driving of an external switch signal. Circulator solutions utilize non-reciprocal devices to achieve unidirectional signal transmission, thereby avoiding crosstalk between the transmitter and receiver. However, circulator solutions have relatively low transmit / receive isolation, and the marine environment poses multi-dimensional challenges to communication systems: firstly, mechanical vibration causes RF device parameter drift; secondly, salt spray corrosion accelerates the aging of RF components; and thirdly, electromagnetic interference (20–100 MHz band) is generated by motors, navigation equipment, etc., on the ship's deck. The isolation performance of time-division duplex mobile communication systems deteriorates sharply in the high-frequency vibration, electromagnetic interference, and salt spray corrosion environment of ships, leading to communication quality degradation. Furthermore, RF switch solutions require precise driving of external switch signals, necessitating customized development by module manufacturers, increasing R&D cycle and cost. Summary of the Invention

[0004] This invention provides a time-division duplex mobile communication system to solve the technical problems of low transmit / receive isolation and long development cycle in existing time-division duplex mobile communication systems.

[0005] This invention provides a time-division duplex mobile communication system, comprising: an electronically scanned antenna, a radio frequency (RF) control device, and a client terminal device; the electronically scanned antenna includes M antenna sectors, where M is a positive integer; the RF control device includes a gating control circuit, a first directional coupler, a signal generation circuit, and M transceiver circuits corresponding to the M antenna sectors; the gating control circuit is configured to monitor the signal quality of the RF signals on the M transceiver circuits and select a target transceiver circuit from the M transceiver circuits to connect to the client terminal device based on the signal quality of the RF signals on the M transceiver circuits; the first directional coupler is connected between the M transceiver circuits and the client terminal device, and the first directional coupler is configured to extract a first RF component from the transmitted signal of the client terminal device; the signal generation circuit is configured to generate a switch control signal based on the first RF component to control the target transceiver circuit to switch between a transmit state and a receive state.

[0006] In some embodiments, the time-division duplex mobile communication system further includes: a second directional coupler connected between the electronically scanned antenna and the M-channel transceiver circuit, the second directional coupler being configured to extract a second radio frequency component from the received signal of the electronically scanned antenna; and a signal generation circuit being configured to generate the switching control signal based on the first radio frequency component and the second radio frequency component.

[0007] In some embodiments, the signal generation circuit includes: a first preprocessing sub-circuit configured to preprocess the first radio frequency component and output a first instantaneous level characterizing the signal strength of the transmitted signal; and a generation sub-circuit configured to acquire a threshold signal and generate the switch control signal based on a comparison result between the first instantaneous level and the threshold signal.

[0008] In some embodiments, the generation sub-circuit includes: a threshold signal sub-circuit configured to generate a threshold level as the threshold signal; and a first comparator with two input terminals correspondingly connected to the output terminal of a first preprocessing sub-circuit and the output terminal of the threshold signal sub-circuit, the output terminal of the first comparator being connected to the control terminal of the M-channel transceiver circuit, the first comparator being configured to: output a high-level signal when the first instantaneous level is greater than the threshold level, to control the target channel transceiver circuit to switch from the receiving state to the transmitting state; and output a low-level signal when the first instantaneous level is less than or equal to the threshold level, to control the target channel transceiver circuit to switch from the transmitting state back to the receiving state.

[0009] In some embodiments, the generation sub-circuit includes: a first analog-to-digital converter (ADC), with its input terminal connected to the output terminal of the first preprocessing sub-circuit, the first ADC being configured to: perform analog-to-digital conversion on a first instantaneous level output by the first preprocessing sub-circuit and output a first instantaneous power; and a processor, with its input pin connected to the output terminal of the first ADC and its output pin connected to the control terminal of the M-channel transceiver circuit, the processor being configured to: acquire a power threshold as the threshold signal, and when the first instantaneous power is greater than the power threshold, output a first switch control signal to control the target channel transceiver circuit to switch from a receiving state to a transmitting state; and when the first instantaneous power is less than or equal to the power threshold, output a second switch control signal to control the target channel transceiver circuit to switch from the transmitting state back to the receiving state.

[0010] In some embodiments, the signal generation circuit includes: a first preprocessing sub-circuit configured to preprocess the first radio frequency component and output a first instantaneous level characterizing the signal strength of the transmitted signal; a second preprocessing sub-circuit configured to preprocess the second radio frequency component and output a second instantaneous level characterizing the signal strength of the received signal; and a generation sub-circuit configured to acquire a threshold signal and generate the switch control signal based on a comparison result of the first instantaneous level, the second instantaneous level, and the threshold signal.

[0011] In some embodiments, the generation sub-circuit includes: a threshold signal sub-circuit configured to generate a threshold level as the threshold signal; a first comparator, with two input terminals correspondingly connected to the output terminals of a first preprocessing sub-circuit and the threshold signal sub-circuit, the first comparator being configured to output a first level signal based on a comparison result between the first instantaneous level and the threshold level; a second comparator, with two input terminals correspondingly connected to the output terminals of the first preprocessing sub-circuit and the second preprocessing sub-circuit, the second comparator being configured to output a second level signal based on a comparison result between the first instantaneous level and the second instantaneous level; and a control signal sub-circuit, with two input terminals correspondingly connected to the output terminals of the first comparator and the second comparator, the output terminal of the control signal sub-circuit being connected to the control terminal of the M-channel transceiver circuit, the control signal sub-circuit being configured to output the switch control signal based on a comparison result between the first level signal and the second level signal.

[0012] In some embodiments, the generation sub-circuit includes: a first analog-to-digital converter (ADC), with its input terminal connected to the output terminal of the first preprocessing sub-circuit, configured to perform analog-to-digital conversion on the first instantaneous level and output a first instantaneous power; a second ADC, with its input terminal connected to the output terminal of the second preprocessing sub-circuit, performing analog-to-digital conversion on the second instantaneous level and outputting a second instantaneous power; and a processor, with its input pin connected to the output terminals of the first and second ADCs, and its output pin connected to the control terminal of the M-channel transceiver circuit, the processor being configured to: acquire a power threshold as the threshold signal; when the first instantaneous power is greater than the power threshold and the first instantaneous power is greater than the second instantaneous power, output a first switch control signal to control the target channel transceiver circuit to switch from the receiving state to the transmitting state; otherwise, generate a second switch control signal to control the target channel transceiver circuit to switch from the transmitting state back to the receiving state.

[0013] In some embodiments, the first preprocessing sub-circuit includes: a first bandpass filter, a first low-noise amplifier, and a first power detector cascaded sequentially with the coupling output terminal of the first directional coupler; the second preprocessing sub-circuit includes: a second bandpass filter, a second low-noise amplifier, and a second power detector cascaded sequentially with the coupling output terminal of the second directional coupler.

[0014] In some embodiments, the first preprocessing subcircuit further includes: a first gain adjustment subcircuit cascaded before the first power detector, the first gain adjustment subcircuit being configured to: adjust the gain of the radio frequency signal processed by the first low-noise amplifier and the first bandpass filter to the operating range of the first power detector; the second preprocessing subcircuit further includes: a second gain adjustment subcircuit cascaded before the second power detector, the second gain adjustment subcircuit being configured to: adjust the gain of the radio frequency signal processed by the second low-noise amplifier and the second bandpass filter to the operating range of the second power detector.

[0015] In some embodiments, the signal generation circuit includes: a power divider configured to divide the first radio frequency component into N radio frequency signals; N preprocessing sub-circuits, each preprocessing sub-circuit configured to preprocess one of the N radio frequency signals and output a corresponding instantaneous level; and a generation sub-circuit configured to acquire a threshold signal and generate the switch control signal based on the comparison result between the N instantaneous levels output by the N preprocessing sub-circuits and the threshold signal.

[0016] In some embodiments, the signal generation circuit includes: a first radio frequency (RF) front-end module connected to the coupling output terminal of the first directional coupler, the first RF front-end module being configured to output a first RF signal after standardizing the first RF component; an RF transceiver connected to the first RF front-end module, the RF transceiver being configured to sample the first RF signal and output a first data stream; and a processor connected to the RF transceiver, the processor being configured to: extract signal features from the first data stream to obtain a first instantaneous power, and generate the switching control signal based on a comparison result between the first instantaneous power and a power threshold.

[0017] In some embodiments, the signal generation circuit includes: a first radio frequency (RF) front-end module connected to the coupling output terminal of the first directional coupler, the first RF front-end module being configured to output a first RF signal after standardizing the first RF component; a second RF front-end module connected to the coupling output terminal of the second directional coupler, the second RF front-end module being configured to output a second RF signal after standardizing the second RF component; an RF transceiver connected to the first RF front-end module and the second RF front-end module, the RF transceiver being configured to output a first data stream after sampling the first RF signal, and to output a second data stream after sampling the second RF signal; and a processor connected to the RF transceiver, the processor being configured to extract signal features from the first data stream to obtain a first instantaneous power, extract signal features from the second data stream to obtain a second instantaneous power, and generate the switch control signal based on a comparison result of the first instantaneous power, the second instantaneous power, and a power threshold.

[0018] In some embodiments, the processor is also connected to the mobile communication module of the client terminal device; the processor is further configured to: obtain multi-dimensional quality parameters characterizing the received signal quality of the mobile communication module from the client terminal device, and process the multi-dimensional quality parameters using a threshold generation strategy matching the scenario of the time-division duplex mobile communication system to obtain the power threshold.

[0019] In some embodiments, the processor is configured to: acquire from the client terminal device multidimensional quality parameters characterizing the received signal quality of the mobile communication module and scene state information of the scenario in which the time-division duplex mobile communication system is located; extract key features from the multidimensional quality parameters and the scene state information; input the extracted key features into a long short-term memory neural network for prediction to output a dynamic threshold compensation factor; and obtain the power threshold based on the dynamic threshold compensation factor and the base threshold.

[0020] Through one or more embodiments provided by the present invention, at least the following technical effects or advantages are achieved: The time-division duplex mobile communication system provided in this invention uses a first directional coupler connected between the M-channel transceiver circuits and the client terminal equipment. This first directional coupler extracts a first radio frequency (RF) component from the transmitted signal of the client terminal equipment. A signal generation circuit generates a switching control signal based on this first RF component to control the switching of the target transceiver circuit between transmit and receive states. This technical solution, by embedding a directional coupler in the RF link, achieves real-time, dynamic monitoring and adaptive processing of the transmitted signal from the client terminal equipment, thereby generating a high-quality switching control signal for transmit / receive switching. This eliminates the need for an external module to provide the switching control signal and replaces the circulator solution. Therefore, it improves the transmit / receive isolation performance of TDD signal processing in a shipboard environment and shortens the development cycle. Attached Figure Description

[0021] To more clearly illustrate the technical solutions in the embodiments of the present invention, the accompanying drawings used in the description of the embodiments will be briefly introduced below. Obviously, the accompanying drawings described below are some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0022] Figure 1 A schematic diagram of the overall architecture of a time-division duplex mobile communication system according to some embodiments of the present invention is shown; Figure 2 The diagram shows a schematic representation of the electronically scanned antenna in some embodiments of the present invention; Figure 3 The following are schematic diagrams illustrating the communication of the duplex mobile communication system in a 5G communication scenario according to some embodiments of the present invention; Figure 4 A schematic diagram of a client terminal device for a split-duplex mobile communication system according to some embodiments of the present invention is shown; Figure 5 A schematic diagram of signal processing for a duplex mobile communication system according to some embodiments of the present invention is shown; Figures 6-23 A schematic diagram of radio frequency switch control of a split-duplex mobile communication system according to some embodiments of the present invention is shown. Detailed Implementation

[0023] To make the objectives, technical solutions, and advantages of this invention clearer, the technical solutions of the embodiments of this invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only a part of the embodiments of this invention, and not all of them. Based on the embodiments of this invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of this invention.

[0024] Figure 1 The overall architecture of a time-division duplex mobile communication system according to some embodiments of the present invention is shown. For example... Figure 1 As shown, the time-division duplex mobile communication system provided in this embodiment of the invention includes: an electronically scanned antenna 10, a radio frequency control device 20, and a client terminal device 30. The electronically scanned antenna 10 includes M antenna sectors 110. The radio frequency control device 20 includes a gating control circuit 210, a first directional coupler 220, a signal generation circuit 230, and M transceiver circuits 240 corresponding to the M antenna sectors 110. The gating control circuit 210 is configured to monitor the signal quality of the radio frequency signals on the M transceiver circuits 240, and select a target transceiver circuit 240-1 from the M transceiver circuits 240 to connect to the client terminal device 30 based on the signal quality of the radio frequency signals on the M transceiver circuits 240. The first directional coupler 220 is connected between the M transceiver circuits 240 and the client terminal device 30, and the first directional coupler 220 is configured to extract a first radio frequency component from the transmitted signal of the client terminal device 30. The signal generation circuit 230 is configured to generate a switch control signal based on a first radio frequency component to control the target transceiver circuit 240-1 to switch between a transmit state and a receive state.

[0025] The time-division duplex mobile communication system provided in this invention is particularly suitable for high-dynamic scenarios such as shipboard and vehicle-mounted environments. The shipboard time-division duplex mobile communication system provides a stable, high-bandwidth, low-latency network connection for ships during navigation, meeting the real-time data transmission needs of crew, passengers, and offshore equipment, and is deeply adapted to the requirements of the dynamic environment of ships.

[0026] The electronically scanned antenna 10 (ESA) has three to six antenna sectors 110. For example... Figure 2As shown, in a shipboard scenario, the electronically scanned antenna 10 is a six-sector directional antenna, comprising six antenna sectors 110 and a scanning control unit 120, achieving precise beam coverage during ship movement. The six-sector directional antenna consists of six independent antenna sectors 110, forming 360° continuous coverage and avoiding blind spots. Each antenna sector 110 contains several radiating elements, ensuring high directivity and high gain. Each antenna sector covers a 60° horizontal viewing angle, balancing coverage range and beam accuracy. The electronically scanned antenna 10 operates in the 2496–2690MHz frequency band to ensure compatibility with existing shipboard communication standards. The scanning control unit 120 controls the phase changes of the radiating elements in the six antenna sectors, causing the beam direction of the electronically scanned antenna 10 to move in space, thereby achieving beam scanning.

[0027] Each transceiver circuit 240 incorporates a miniature coupler that extracts a portion of the RF signal power (e.g., 5%) from that circuit in real time, generating a monitoring signal to assess the signal quality of that RF signal. The coupling process of the miniature coupler introduces signal interference of less than -30dB, ensuring the integrity of the main signal.

[0028] It is understood that the gating control circuit 210 in the embodiments of the present invention includes a gating sub-circuit 211, a monitoring sub-circuit 212, and a switching sub-circuit 213.

[0029] The selection sub-circuit 211 is responsible for selecting one of the M monitoring signals to switch to the monitoring sub-circuit 212, and selecting one of the M transceiver circuits to switch to the customer terminal equipment 30.

[0030] The monitoring sub-circuit 212 is responsible for evaluating the signal quality of the extracted monitoring signal. For example, it parses the received monitoring signal and extracts key signal quality indicators such as Reference Signal Received Power (RSRP), Reference Signal Received Quality (RSRQ), Signal to Interference plus Noise Ratio (SINR), and Bit Error Rate (BER) from the received monitoring signal, with the time synchronization error between each indicator ≤0.5ms.

[0031] The switching sub-circuit 213 is responsible for coordinating the dynamic switching of the M transceiver circuits 240. The switching sub-circuit 213 polls the key signal quality indicators from the M monitoring signals extracted from the M transceiver circuits 240 at a fixed period. This fixed period can be dynamically adjusted according to the actual environment to ensure optimal monitoring efficiency in changing environments. The switching sub-circuit 213 performs a weighted sum calculation on each key signal quality indicator collected from the monitoring signal of the current transceiver circuit 240 to obtain the signal quality score of the RF signal on the current transceiver circuit 240. For example, the signal quality score Score = α × SINR + β × RSRP + γ × RSRQ, where α, β, and γ correspond to the weighting coefficients of different key signal quality indicators. After obtaining the signal quality scores of the RF signals on the M transceiver circuits 240, the optimal channel is determined based on these scores, and a control command is issued to switch to the target transceiver circuit 240 as the optimal channel. The switching process can use hard handover instead of soft handover to reduce the risk of data interruption.

[0032] like Figure 3 As shown, Figure 3 In a 5G communication scenario, the radio frequency control device 20, the electronically scanned antenna 10, and the customer terminal equipment 30 are connected to a system architecture that enables the transmission and reception of 5G dual-band (N41 band and N28 band) signals. The system dynamically selects the optimal channel in a 5G communication scenario to ensure that the signal quality of the customer terminal equipment 30 with a 5G module is optimal.

[0033] Understandably, the client terminal device 30 is a key hardware component for mobile network access user terminals, converting base station signals into network connections usable by the user terminal. For example... Figure 4 As shown, taking a client terminal device 30 that supports 5G communication as an example, it includes a 5G module, a WiFi physical layer chip (WiFi PHY), a 2.5G Ethernet controller (QCN8108), a local area network physical layer chip (LAN PHY), a WiFi radio frequency front end, and a 5G radio frequency front end.

[0034] The radio frequency control device 20 is a device that integrates various radio frequency control functions. For example... Figure 5As shown, the M transceiver circuits 240 provide M independent signal channels for RF signal enhancement. Each transceiver circuit 240 includes a switchable receive enhancement sub-circuit 241 and a transmit enhancement sub-circuit 242. The receive enhancement sub-circuit 241 is equipped with a filter F1 and an amplifier A1. The transmit enhancement sub-circuit 242 is equipped with a filter F2 and an amplifier A2. The amplifiers A1 and A2 can both include low-noise amplifiers (LNAs) and power amplifiers (PAs), etc.

[0035] Each transceiver circuit 240's receive enhancement sub-circuit 241 receives the RF signal from one antenna sector 110 of the electronically scanned antenna 10, amplifies, filters, and suppresses noise, and then outputs a high-quality RF signal to the mobile communication module 310 of the client terminal equipment 30. Each transceiver circuit 240's transmit enhancement sub-circuit 242 receives the RF signal from the mobile communication module 310 of the client terminal equipment 30, amplifies, filters, and modulates it, and then transmits it to the target area through one antenna sector 110 of the electronically scanned antenna 10. The gain range of each transceiver circuit 240 is 20–30 dB, enabling the electronically scanned antenna 10 to operate stably within a dynamic range of -120 dBm to +30 dBm. The working principle of TDD signal processing is to divide the communication time into uplink and downlink time slots. In the uplink time slot, the transmit enhancement sub-circuit 242 is active, and the receive enhancement sub-circuit 241 is off; in the downlink time slot, the receive enhancement sub-circuit 241 is active, and the transmit enhancement sub-circuit 242 is off.

[0036] like Figure 5 As shown, in some embodiments, each transceiver circuit 240 further includes a first RF switch K1 and a second RF switch K2. Both the first RF switch K1 and the second RF switch K2 are 1-to-2 RF switches. The common terminal of the first RF switch K1 is connected to the electronically scanned antenna 10, and the two throwing terminals are respectively connected to one end of the transmit enhancement sub-circuit 242 and the receive enhancement sub-circuit 241. The common terminal of the second RF switch K2 is connected to the client terminal equipment 30, and the two throwing terminals are respectively connected to the other end of the transmit enhancement sub-circuit 242 and the receive enhancement sub-circuit 241.

[0037] It is understood that the first directional coupler 220 is a four-port network, including: an input terminal, a through output terminal, a coupled output terminal, and an isolation terminal. The connection relationship between the first directional coupler 220 and the M-channel transceiver circuits 240 and the client terminal equipment 30 is as follows: the input terminal of the first directional coupler 220 is connected to the common terminal of the second RF switch K2 in each transceiver circuit 240; the through output terminal of the first directional coupler 220 is connected to the client terminal equipment 30; and the coupled output terminal of the first directional coupler 220 is connected to the input terminal of the signal generation circuit 230. By using the first directional coupler 220 located at the front end of the client terminal equipment 30, non-intrusive coupling of the transmitted signal of the client terminal equipment 30 is achieved, coupling out a portion of the RF component from the transmitted signal of the client terminal equipment 30, namely: the first RF component.

[0038] The first directional coupler 220, as a passive device, has a coupling coefficient of 10~30dB and a directivity greater than 30dB. Through its coupling structure (e.g., a four-port network), it extracts a weak first radio frequency component from the transmitted signal on the main signal path of the client terminal equipment 30. The coupling power accounts for 1%–10%, and the extracted first radio frequency component is directed to an independent monitoring channel, namely the guiding signal generation circuit 230, while minimizing interference to the main signal path. The directional coupling characteristic of the first directional coupler 220 ensures that the coupled signal contains only the forward transmission component, effectively suppressing the reverse reflection signal.

[0039] In some embodiments, the signal generation circuit 230 is configured to: generate switching control signals for controlling the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 based on the first RF component, and control the first RF switch K1 and the second RF switch K2 to switch between a state where the receiver enhancement sub-circuit 241 in the target transceiver circuit 240-1 is turned on and a state where the transmitter enhancement sub-circuit 242 in the target transceiver circuit 240-1 is turned on. It should be understood that when the first RF switch K1 and the second RF switch K2 are in the state where the receiver enhancement sub-circuit 241 in the target transceiver circuit 240-1 is turned on, the receiver enhancement sub-circuit 241 in the target transceiver circuit 240-1 is connected to the corresponding antenna sector 110 and the client terminal device 30, and the target transceiver circuit 240 is in a receiving state. When the first RF switch K1 and the second RF switch K2 are in the state of conducting the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1 is connected to the corresponding antenna sector 110 and the customer terminal equipment 30, and the target transceiver circuit 240 is in the transmit state.

[0040] like Figures 6 to 12As shown, in some embodiments, the signal generation circuit 230 includes a first preprocessing sub-circuit 231 and a generation sub-circuit 232. The coupling output terminal of the first directional coupler 220 is connected to the input terminal of the first preprocessing sub-circuit 231, the output terminal of the first preprocessing sub-circuit 231 is connected to the input terminal of the generation sub-circuit 232, and the output terminal of the generation sub-circuit 232 is connected to the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The first preprocessing sub-circuit 231 is configured to preprocess the first RF component and output a first instantaneous level characterizing the signal strength of the transmitted signal from the client terminal device 30. The first RF component is preprocessed by the first preprocessing sub-circuit 231 so that the RF signal output by the first preprocessing sub-circuit 231 conforms to the RF measurement specifications. The generation sub-circuit 232 is configured to: acquire a threshold signal and generate a switch control signal based on the comparison result between the first instantaneous level and the threshold signal, so as to control the state of the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1, so as to switch the target transceiver circuit 240-1 between the transmit state and the receive state.

[0041] like Figures 6 to 12 As shown, the internal circuit structure of the first preprocessing sub-circuit 231 includes a first standard processing module 2311 and a first power detector 2312. The first standard processing module 2311 is configured to perform standard processing on the first radio frequency component. The radio frequency signal after standard processing meets the measurement conditions of the first power detector 2312. The first power detector 2312 performs power measurement on the radio frequency signal after standard processing by the first standard processing module 2311 to obtain the first instantaneous level.

[0042] like Figures 6 to 12As shown, in some embodiments, the first standard processing module 2311 includes a first bandpass filter (BPF) BPF1 and a first low-noise amplifier (LNA) LNA1 arranged in series. The first bandpass filter BPF1 and the first low-noise filter LNA1 sequentially suppress noise and filter the bandwidth of the first radio frequency component, ensuring that the standard-processed radio frequency signal meets the measurement conditions of the first power detector 2312 before entering the first power detector 2312. It should be understood that the principle of filtering before amplification can be followed, with the coupling output of the first directional coupler 220 cascaded with the first bandpass filter BPF1 and the first low-noise amplifier LNA1, and the output of the first low-noise amplifier LNA1 connected to the first power detector 2312. In other embodiments, the coupling output of the first directional coupler 220 is cascaded with a first low-noise amplifier LNA1 and a first bandpass filter BPF1. The output of the first bandpass filter BPF1 is connected to a first power detector 2312. The first radio frequency component is then subjected to bandpass filtering, amplification, low noise, and noise suppression before entering the first power detector 2312 for power measurement.

[0043] In some embodiments, the center frequency of the first bandpass filter BPF1 matches the operating frequency band of the client terminal equipment 30, and the bandwidth of the first bandpass filter BPF1 is the coverage bandwidth of the transmitted signal of the client terminal equipment 30, so as to suppress adjacent channel interference and high-frequency noise. The gain of the first low-noise amplifier LNA1 is set to 20-30dB, and the noise figure (NF) is ≤1.5dB, ensuring that the signal-to-noise ratio (SNR) of weak signals below -100 dBm is greater than 10dB. The first power detector 2312 can be a power detector used to measure the root mean square power level (RMS), referred to as the RMS power detector. The RMS power detector converts the radio frequency signal after standard processing of the first radio frequency component into a root mean square power level value. The accuracy of the first power detector 2312 affects the reliability of the system enable determination; therefore, the error of the first power detector 2312 is less than ±0.5 dB.

[0044] like Figures 6 to 8As shown, in some embodiments, the generation sub-circuit 232 includes a threshold signal sub-circuit 2321 and a first comparator C1. The two input terminals of the first comparator C1 are respectively connected to the output terminals of the first preprocessing sub-circuit 231 and the threshold signal sub-circuit 2321. The output terminal of the first comparator C1 is connected to the control terminal of the M-channel transceiver circuit 240. The threshold signal sub-circuit 2321 is configured to generate a threshold level as a threshold signal. The first comparator C1 is configured to: when the first instantaneous level is greater than the threshold level, output a high-level signal as a switch control signal to control the target transceiver circuit 240-1 to switch from the receiving state to the transmitting state; when the first instantaneous level is less than or equal to the threshold level, output a low-level signal as a switch control signal to control the target transceiver circuit 240-1 to switch back from the transmitting state to the receiving state.

[0045] like Figures 6 to 8 As shown, the two input terminals of the first comparator C1 are connected to the output terminals of the first preprocessing sub-circuit 231 and the threshold signal sub-circuit 2321, respectively. Specifically, the non-inverting input terminal of the first comparator C1 is connected to the output terminal of the first power detector 2312, and the inverting input terminal of the first comparator C1 is connected to the output terminal of the threshold signal sub-circuit 2321. The control terminal of each transceiver circuit 240 is the control terminal of the first RF switch K1 and the second RF switch K2 in that transceiver circuit 240. That is, the output terminal of the first comparator C1 is connected to the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The first comparator C1 is configured to compare a first instantaneous level with a threshold level, and generate a switch control signal based on the comparison result to drive the states of the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1, thereby switching the target transceiver circuit 240-1 between transmit and receive states. Specifically, when the instantaneous level is greater than the threshold level, the first comparator C1 outputs a high-level signal, causing the first RF switch K1 and the second RF switch K2 to select the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the receiving state to the transmitting state; when the instantaneous level is less than or equal to the threshold level, the first comparator C1 outputs a low-level signal, causing the first RF switch K1 and the second RF switch K2 to select the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the transmitting state back to the receiving state.

[0046] like Figure 6As shown, in some embodiments, the threshold signal subcircuit 2321 may generate a threshold level using a threshold generation mechanism based on an adjustable resistor network AT1. The threshold signal subcircuit 2321 is a cascade of a reference voltage source VREF and an adjustable resistor network AT1, with the reference voltage provided by the reference voltage source VREF. For example, the reference voltage source VREF provides a reference voltage with an accuracy of ±0.1%. The adjustable resistor network AT1 is connected between the reference voltage source VREF and the inverting input of the first comparator C1. Based on manual voltage division adjustment of the adjustable resistor network AT1, the threshold level input to the first comparator C1 can be continuously and manually adjusted.

[0047] The cascading of the reference voltage source VREF and the adjustable resistor network AT1 to achieve manual continuous adjustment of the threshold level has several drawbacks: 1. Poor stability: temperature drift and time drift cause parameter drift, resulting in insufficient reliability; 2. Low accuracy and poor consistency; 3. Manual adjustment cannot achieve precise matching; mechanical structural defects: poor contact, easy wear, and weak anti-interference ability; 4. Inability to automate adjustment: poor adaptability to dynamic scenarios; 5. Low debugging efficiency and poor adaptability to mass production; 6. Physical limitations: large size, low integration, and unsuitable for miniaturization design. In view of the above drawbacks, in some other embodiments, a threshold level can be generated using an online manual adjustment mechanism.

[0048] like Figure 7 As shown, to achieve online manual adjustment of the threshold level, in another embodiment, the threshold signal sub-circuit 2321 may include: a system-on-chip (SOC), a digital-to-analog converter (DAC) DAC1, and a buffer. The SOC provides a configuration interface for online configuration of the power threshold. The SOC is connected to the input of the DAC, and the output of the DAC is connected to the inverting input of the first comparator C1 via the buffer. The SOC is configured to provide a power threshold to the DAC based on the online configured power threshold. The DAC generates a threshold level as a threshold signal based on the power threshold provided by the SOC and a reference voltage (accuracy ±0.1%) provided by the reference voltage source VREF. The threshold level is passed to the first comparator C1 via the buffer. In some embodiments, the buffer is a low-noise buffer with a gain greater than 100 dB and a bandwidth greater than 100 MHz. The buffer ensures signal integrity and eliminates noise and distortion during transmission. The SOC implements online configuration of the power threshold through a configuration interface of a serial port and / or a network port. The serial port uses the UART protocol to adjust the power threshold in real time; the network port uses the TCP / IP protocol to adjust the power threshold in real time (response time < 50 ms).

[0049] The configuration parameters of the threshold signal sub-circuit 2321 are shown in Table 1 below: Table 1. Parameter categories Typical value Engineering significance Accuracy of digital-to-analog converter ±0.1% Ensure the stability of the threshold level Buffer bandwidth >100 MHz Eliminate distortion in high-speed signal transmission Configure interface latency <50 ms Meets real-time dynamic calibration requirements Minimum adjustment step size 0.1 dB Adaptable to low signal-to-noise ratio scenarios (SNR<5 dB) Reset mechanism Triggered by software commands Ensure rapid system recovery in abnormal situations. like Figure 8 As shown, in some embodiments, the threshold signal sub-circuit 2321 includes: a State Controller (SOC), a digital potentiometer, and a reference voltage source VREF. The SOC provides a configuration interface for online configuration of the threshold signal. The SOC is connected to the input of the digital potentiometer, and the output of the digital potentiometer is connected to the inverting input of the first comparator C1. The reference voltage source VREF (such as TP4057) provides a base reference voltage (accuracy ±0.1%) for the digital potentiometer. Based on the online configured power threshold, the SOC controls the digital potentiometer to change the resistor division voltage of the digital potentiometer, thereby adjusting the threshold level input to the first comparator C1 based on the reference reference voltage provided by the reference voltage source VREF and the power threshold provided by the SOC. It should be noted that in this embodiment, the SOC implements online configuration of the power threshold through a configuration interface of serial port and / or network port.

[0050] The above Figures 6 to 8 In the various embodiments shown, the generation sub-circuit 232 relies entirely on the first comparator C1, generating the switch control signals for controlling the first RF switch K1 and the second RF switch K2 entirely through an analog voltage comparator. However, generating switch control signals based on an analog voltage comparator has some drawbacks: 1. Due to the analog characteristics of the first comparator C1, the parameters drift significantly, resulting in low accuracy and poor stability of the threshold level; 2. It only supports simple threshold logic and cannot adapt to complex scenarios, resulting in poor functional flexibility; 3. It is sensitive to analog noise and susceptible to electromagnetic interference, resulting in weak anti-interference capability; 4. It cannot seamlessly integrate with digital systems, resulting in low integration and high expansion costs; 5. It has a limited dynamic range and cannot adapt to wide-amplitude signal scenarios.

[0051] To overcome the shortcomings of analog voltage comparators in generating switch control signals, this invention also proposes some embodiments based on digital comparison to generate switch control signals that control the switching of the first RF switch K1 and the second RF switch K2.

[0052] like Figures 9 to 10As shown, to generate switch control signals for controlling the first RF switch K1 and the second RF switch K2 based on digital comparison, in some embodiments, the generation sub-circuit 232 includes: a first analog-to-digital converter (ADC1) and a processor 239. The input terminal of the first ADC1 is connected to the output terminal of the first preprocessing sub-circuit 231, that is, connected to the output terminal of the first power detector 2312 in the first preprocessing sub-circuit 231. The input pin of the processor 239 is connected to the output terminal of the first ADC1. The output pin of the processor 239 is connected to the control terminal of the M-channel transceiver circuit 240, that is, connected to the control terminals of the first RF switch K1 and the second RF switch K2. The first ADC1 is configured to: perform analog-to-digital conversion on the first instantaneous level output by the first preprocessing sub-circuit 231 and output a first instantaneous power. The first ADC1 samples the first instantaneous level output by the first power detector 2312 at a preset sampling rate greater than or equal to 100 MS / s to convert it into a digital signal of the first instantaneous power. The first analog-to-digital converter (ADC1) transmits the first instantaneous power of the digital signal to the processor 239. The processor 239 is configured to: acquire a power threshold as a threshold signal; compare the first instantaneous power acquired by the first ADC1 with the power threshold; when the first instantaneous power is greater than the power threshold, output a first switch control signal to control the target transceiver circuit 240-1 to switch from the receiving state to the transmitting state; when the first instantaneous power is less than or equal to the power threshold, output a second switch control signal to control the target transceiver circuit 240-1 to switch from the transmitting state back to the receiving state. The first switch control signal and the second switch control signal are different switch control signals.

[0053] Understandably, the acquisition of the first instantaneous power is accomplished collaboratively by the first power detector 2312 and the first analog-to-digital converter ADC1. The first power detector 2312 is an RMS power detector. Since the RMS power detector measures the power of the input signal based on the square integral algorithm, it can accurately reflect the actual energy of the input signal. The measurement accuracy of the RMS power detector can reach ±1.2dB, which is significantly better than that of the average power detector (error ≥ ±2.5 dB), especially in scenarios with sudden changes in signal envelope (such as sudden interference and multipath effects). The first analog-to-digital converter ADC1 in the generation sub-circuit 232 can be a high-speed analog-to-digital converter with a resolution greater than or equal to 10 bits and a sampling rate greater than or equal to 100MS / s (e.g., TIADS1299). Key parameters of the first analog-to-digital converter (ADC1) include: sampling rate: ≥100 MS / s (satisfying Nyquist's theorem); resolution: ≥10 bits (quantization accuracy 0.01 dB); dynamic range: ≥80 dB (covering the typical transmit power range of a CPE); signal-to-noise ratio: ≥80 dB (ensuring measurement accuracy); conversion time: ≤10 ns (ensuring high-speed signal processing). The output of the first ADC1 is a time-domain continuous digital signal. The first instantaneous power sampled at any given time includes a precise power measurement value (unit: dBm) and timestamp information, providing high-quality input for subsequent comparison with power thresholds. This design ensures the system's measurement accuracy and real-time performance in high-dynamic scenarios.

[0054] It should be understood that the first switch control signal generated by the processor 239 is used to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to be in the state of conducting the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the receive state to the transmit state; the generated second switch control signal is used to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to be in the state of conducting the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the transmit state back to the receive state.

[0055] In some embodiments, the processor 239 introduces a hysteresis threshold when generating the first switch control signal. That is, the first switch control signal is generated when the first instantaneous power is greater than the sum of a power threshold and a preset hysteresis threshold; and the second switch control signal is generated when the first power threshold is less than or equal to the power threshold. For example, the hysteresis threshold is set to 0.5 dB. The original instantaneous power sampled by the first analog-to-digital converter (ADC1) fluctuates greatly, exhibiting instantaneous fluctuations. The processor 239 uses a sliding window averaging filter algorithm to average and filter the original power sampling data sampled by the first ADC1. The average power after filtering and smoothing is used as the first instantaneous power, thereby eliminating the influence of instantaneous fluctuations. The window size of the sliding window is adjusted according to actual needs.

[0056] It should be noted that the power threshold acquired by processor 239 is a digital signal. Processor 239 can acquire the power threshold in two ways to ensure the system's adaptability in different application scenarios.

[0057] In some embodiments, the power threshold acquired by the processor 239 can be a pre-configured static threshold, which is hardware-implanted in the processor 239's read-only memory (ROM), and its configuration process requires no external intervention. Upon system startup, the processor 239 reads the preset static threshold from the ROM and stores it in an internal register. This static threshold remains unchanged throughout the system's lifecycle, making it suitable for stable environments (such as home fixed networks and low-interference scenarios). The configuration of the static threshold is typically completed at the system's factory, using mask programming to write the preset static threshold, ensuring it cannot be tampered with.

[0058] In other embodiments, the power threshold acquired by the processor 239 is a dynamic threshold. The processor 239 receives remote commands for power threshold configuration via a serial port and / or a network port to update the power threshold. The serial port uses the RS-485 / UART protocol to receive threshold update commands; the network port receives threshold update commands via Ethernet (TCP / IP protocol).

[0059] Because the operating range of the RMS power detector is limited by device nonlinearity (such as diode conduction threshold and amplifier saturation characteristics), noise floor (affecting the lower boundary power), and maximum withstand power (affecting the upper boundary power), the actual usable operating range is far lower than the theoretical value. To achieve real-time, high-precision monitoring and dynamic control of the transmitted signal from the customer terminal equipment 30, it is necessary to resolve the compatibility issue between the wide power fluctuation range of the coupled first RF component and the narrow operating range of the first power detector 2312. For example... Figures 10 to 11As shown, based on the digital comparison to generate the control signal, the first standard processing module 2311 in the first preprocessing sub-circuit 231 further includes a first gain adjustment sub-circuit. This first gain adjustment sub-circuit is cascaded before the first power detector 2312. The first gain adjustment sub-circuit is configured to, under the control of the processor 239 in the generation sub-circuit 232, adjust the gain of the radio frequency signal before it enters the first power detector 2312, so that the signal power of the adjusted radio frequency signal is within the operating range of the first power detector 2312. That is, the gain of the radio frequency signal processed by the first low-noise amplifier LNA1 and the first bandpass filter BPF1 is adjusted to the operating range of the first power detector 2312.

[0060] like Figures 10 to 11 As shown, in some embodiments, the first gain adjustment sub-circuit is configured to adjust the gain of the radio frequency signal after it has been amplified and bandpass filtered by the first low-noise amplifier LNA1 and the first bandpass filter BPF1 before inputting it to the first power detector 2312.

[0061] like Figure 10 As shown, in some embodiments, the first gain adjustment sub-circuit can be an Automatic Gain Control (AGC) circuit (AGC1). During the power measurement of the transmitted signal from the client terminal equipment 30, the dynamic change of signal power is the main factor affecting the measurement accuracy. When the signal power input to the first power detector 2312 exceeds the operating range of the first power detector 2312, it will lead to measurement distortion, limited dynamic range, or degraded system performance. The Automatic Gain Control (AGC1) circuit automatically adjusts the amplification factor according to the signal power, so that the signal power entering the first power detector 2312 is stabilized within the operating range of the first power detector 2312, thereby improving the accuracy of power measurement and the overall stability of the system. Specifically, by adding the Automatic Gain Control (AGC1) circuit to the first standard processing module 2312, the power measurement error can be controlled within ±0.3dB, thereby improving the accuracy of power measurement. It supports a larger input power dynamic range and also has a suppression capability of more than 90% for instantaneous power surges. Therefore, the added automatic gain control circuit AGC1 helps improve the accuracy of power measurement by the first power detector 2312 and the overall stability of the system.

[0062] In some embodiments, the automatic gain control circuit AGC1 is controlled by the processor 239 using a dual-loop AGC architecture: an outer loop is the power tracking loop, and an inner loop is the gain regulation loop. The outer loop monitors the power change of the input signal to the first power detector 2312 in real time, calculating the deviation between the instantaneous level measured by the first power detector 2312 and the threshold level to obtain a power deviation signal. The outer loop can employ a sliding window averaging filter technique to eliminate the influence of instantaneous fluctuations on power measurement, ensuring the accuracy of power tracking. The power deviation signal output by the outer loop serves as the input to the inner loop. The inner loop outputs a gain adjustment based on the power deviation signal provided by the outer loop. This gain adjustment is used to dynamically adjust the gain value of the programmable gain amplifier (PGA) in the automatic gain control circuit AGC1.

[0063] Processor 239, based on rigorous timing control and mathematical modeling, ensures high-precision, low-latency gain adjustment: First power detector 2312 measures the instantaneous level (in dBm) of the input signal in real time at a preset sampling rate (e.g., 100 MS / s). Processor 239 is configured to calculate the power deviation between the first instantaneous level (Pcurrent) currently sampled by first power detector 2312 and the upper boundary power (PH) and lower boundary power (PL) constituting the operating range of first power detector 2312. The resulting power deviation signal includes an upper power deviation signal and a lower power deviation signal. The lower power deviation signal ΔPL = Pcurrent - PL, and the upper power deviation signal ΔPH = PH - Pcurrent. Based on the upper and lower power deviation signals, a gain adjustment amount is determined, and the gain value of the programmable gain amplifier in automatic gain control circuit AGC1 is adjusted accordingly: when ΔPL < 0, the gain is increased by a certain amount; when ΔPH < 0, the gain is decreased by a certain amount, so that the signal power output by automatic gain control circuit AGC1 falls within the operating range of first power detector 2312. It also presets upper and lower limits for gain adjustment to prevent the gain adjustment from exceeding the adjustable range of the programmable gain amplifier. When the gain adjustment approaches the upper or lower limit of the programmable gain amplifier's adjustable range, the gain adjustment is automatically reduced to ensure the controllability of the gain adjustment.

[0064] like Figure 11As shown, in some other embodiments, the first gain adjustment sub-circuit can be an amplifier array BLNA1, BLNA2... connected in series between the first power detector 2312 and the first directional coupler 220. The amplifier array is a cascade of multiple bypassable low-noise amplifiers, each of which is a low-noise amplifier with an RF bypass switch. Various gain levels are implemented using combinations of multiple bypassable low-noise amplifiers in the amplifier array. The multiple bypassable low-noise amplifiers are configured with a stepped gain increase, meaning the gain of each bypassable low-noise amplifier increases by a factor of 1 compared to the previous stage. The gain relationships of each bypassable low-noise amplifier stage satisfy the following Table 2: Table 2. Gain relationships of bypassable low-noise amplifiers at each stage Amplifier array with bypassable low-noise amplifier stages 1-N Gain BLNA1 G1=x BLNA2 G2=2·G1 BLNAn Gn = 2·G(n-1) The gain of the first-stage bypassable low-noise amplifier BLNA1 is G1=x, and the gain of the nth-stage bypassable low-noise amplifier BLNAn is Gn=2·G(n-1) (n≥2, and n is a positive integer). Continuous gain adjustment is achieved by controlling the on / off states of the RF bypass switches of each stage of the bypassable low-noise amplifier. By combining multiple stages of bypassable low-noise amplifiers in the amplifier array, the limitations of traditional fixed or discrete gain adjustment are overcome, achieving continuously adjustable gain resolution. By dynamically switching the operating and bypass states of each stage of the bypassable low-noise amplifier, even when the transmitted signal power fluctuates over a wide range, it is always precisely controlled within the operating range of the first power detector 2321. This solves the core compatibility contradiction between wide fluctuations in coupled signal power and narrow effective operating range of the detector, thus improving the dynamic range of the system's transmitted and received signals.

[0065] In some embodiments, the processor 239 in the generation sub-circuit 232 serves as the control core. Based on the measurement results of the first power detector 2321, adaptive switching of different gain levels is achieved. The closed-loop process of the processor 239 controlling the adaptive switching of different gain levels is as follows: The first analog-to-digital converter ADC1 in the generation sub-circuit 232 acquires the instantaneous level output by the first power detector 2312 at a preset sampling rate (e.g., 100 MS / s). The processor 239 calculates the average power value of the sampled instantaneous power in real time. The average power value is compared with the upper and lower boundary power of the operating range of the first power detector 2312. Based on the comparison result, a control signal is output to the bypass circuit of each low-noise amplifier in the multi-stage bypassable low-noise amplifier array to achieve gain level control. For example, the upper boundary power can be preset to P_high = +15 dBm, and the lower boundary power can be preset to P_low = -55 dBm.

[0066] A hysteresis threshold (±2dB) can be introduced to avoid frequent switching of gain levels. The ±2dB hysteresis threshold design can reduce more than 90% of invalid switching, providing a key guarantee for stable system operation. Taking the upper and lower boundary power corresponding to the operating range of the first power detector 2312 as an example, with a preset +2dB rising hysteresis threshold and a -2dB falling hysteresis threshold; when the average power value exceeds the upper boundary power of the first power detector 2312 during the rising process and reaches the rising hysteresis difference of +2dB, the gain level is triggered to be lowered; when the average power value falls below the lower boundary power of the first power detector 2312 during the falling process and reaches the falling hysteresis difference of -2dB, the gain level is triggered to be higher.

[0067] In some embodiments, the first RF switch K1 and the second RF switch K2 also have built-in status detection pins connected to the input pins of the processor 239. The first RF switch K1 and the second RF switch K2 feed back the actual status to the processor 239, which is used by the processor 239 to perform closed-loop verification of the status of the target transceiver circuit 240-1.

[0068] All the above embodiments employ online or offline manual configuration of power thresholds, or use static thresholds, which all have significant limitations, especially in complex, dynamic, or high-requirement scenarios. The following problems exist: High subjectivity, reliance on experience, and poor consistency: Manually configured power thresholds rely entirely on the operator's experience and judgment, lacking objective data support. Power thresholds set by different people at different times may vary greatly. Manually configured power thresholds are relatively static; the system's operating environment, data distribution, and signal characteristics are often dynamically changing, and manual adjustment of power thresholds cannot respond in real time. Manually configured power thresholds are usually only applicable to specific scenarios; when the system migrates to a new scenario, the threshold signal will completely fail and requires re-adjustment. Most systems' thresholds need to balance multiple indicators, and manual adjustment cannot accurately find the optimal balance point. Manually adjusted threshold signals lack tolerance to noise and outliers; in extreme situations (such as sudden interference or data anomalies), the system is prone to crashing.

[0069] To solve these problems, such as Figure 12 , Figure 18 , Figure 21 and Figure 23 As shown, in some embodiments, the processor 239 is also connected to the mobile communication module 310 of the client terminal device 30. The processor 239 is also configured to: obtain multi-dimensional quality parameters characterizing the received signal quality of the mobile communication module 310 from the client terminal device 30, and process the obtained multi-dimensional quality parameters using a threshold generation strategy that matches the scenario of the time-division duplex mobile communication system to obtain a power threshold.

[0070] With the processor 239 in the generator sub-circuit 232 as the control core, the processor 239 obtains multi-dimensional quality parameters characterizing the received signal quality of the mobile communication module 310 from the mobile communication module 310 of the client terminal equipment 30, which may include key quality indicators such as RSRP, RSRQ, and SINR.

[0071] To achieve accurate and adaptive generation of the power threshold, in some embodiments, the processor 239 in the generation sub-circuit 232 uses an adaptive history filtering weighting method or a Long Short-Term Memory (LSTM) intelligent compensation algorithm to process multi-dimensional quality parameters to obtain the power threshold.

[0072] In other embodiments, threshold generation strategies corresponding to different scenarios are pre-established. Threshold generation strategies and multi-dimensional quality parameters matching the scenario of the time-division duplex mobile communication system are used to generate the power threshold. The threshold generation strategies for various scenarios are shown in Table 3 below: Table 3. Threshold generation strategy Scene Fixed threshold Initial deployment, interference-stable scenarios Adaptive historical filtering weighting method Common scenarios such as cities and suburbs LSTM intelligent compensation algorithm High-dynamic scenarios such as high-speed rail and ships The adaptive historical filtering method dynamically generates power thresholds based on historical data. It dynamically adjusts the power thresholds by using statistical characteristics (mean, standard deviation) within a sliding window, so that the power thresholds can adapt to environmental changes without manual configuration.

[0073] The process of generating power thresholds based on adaptive history filtering by processor 239 includes: for each dimension of quality parameter, adaptive filtering is performed on the n parameter values ​​of that dimension of quality parameter collected from n sampling points within the time window: θ=μ+k σ, where μ is the mean of the n parameter values ​​of the quality parameter of this dimension sampled n times within the time window, σ is the standard deviation of the n parameter values ​​of the quality parameter of this dimension sampled n times within the time window, k is the adaptive coefficient based on scene dynamic adjustment, usually 1.0-1.5, and θ is the parameter value after adaptive filtering. Then, the parameter values ​​of each dimension of the quality parameter after adaptive filtering are weighted to update the power threshold. The updated power threshold is referenced in the following formula (1): P TH =α×Pbase+β×RSRP'+γ×RSRQ'+δ×SINR'(1) Among them, P TH The updated power threshold is Pbase, the base threshold is RSRP', RSRQ', and SINR' are the adaptive filtering results of key signal quality indicators in each dimension, and α, β, γ, and δ are the corresponding weighting coefficients.

[0074] The mathematical expression of a Long Short-Term Memory (LSTM) neural network revolves around the cellular state (long-term memory) and the hidden state (short-term memory). It achieves selective retention and updating of information through forgetting gates, input gates, and output gates. Specific formulas include: The forget gate controls the proportion of the cell's state retained from the previous moment: ; The input gate controls the proportion of the current input that updates the cell state. ; Cell candidates (currently entered candidate update values): ; Cell state update (long-term memory update): ; Output gate (controls the output ratio of cell state to hidden state): ; Hidden state update (output of short-term memory): ; in, for The input vector at time step; for Hidden state at any given moment (short-term memory); for Cellular state at any given moment (long-term memory); Weight matrix corresponding to phylum / cell candidates; : Bias vectors corresponding to gate and cell candidates; : sigmoid activation function, output range ; Represents the hyperbolic tangent activation function, with an output range of , used to adjust the information amplitude; This represents a vector concatenation operation; This represents the element-wise multiplication operation.

[0075] In some embodiments, the input to the Long Short-Term Memory (LSTM) neural network consists of key features extracted from information such as RSRP, RSRQ, SINR, sailing speed, and historical switching records. The output is a dynamic threshold compensation factor, which ranges from -0.5 to +0.5. The training data used to train the LSM neural network covers various scenarios, including urban areas, suburbs, high-speed rail, and ocean. The model structure is a two-layer LSTM, with a linear activation function used in the output layer. The LSM neural network predicts scene changes within a future time period (e.g., 100ms) and generates a dynamic threshold compensation factor that matches the scene based on the prediction results. .

[0076] Based on the aforementioned Long Short-Term Memory (LSTM) neural network, in some embodiments of the present invention, the processor 239 is also connected to the mobile communication module 310 of the client terminal device 30. The processor 239 is further configured to: acquire multidimensional quality parameters characterizing the received signal quality of the mobile communication module 310 and scene state information of the time-division duplex mobile communication system from the client terminal device 30; extract key features from the multidimensional quality parameters and scene state information; input the extracted key features into the LTM neural network for prediction to output a dynamic threshold compensation factor; and obtain a power threshold based on the dynamic threshold compensation factor and a base threshold.

[0077] Specifically, multi-dimensional information such as RSRP, RSRQ, SINR, and navigation speed is acquired from the client terminal device 30. Key features (such as user network speed change rate and interference source type) are extracted from the acquired multi-dimensional information. The extracted key features are then input into a long short-term memory neural network for prediction to output a dynamic threshold compensation factor. The power threshold is updated based on the dynamic threshold compensation factor output by the long short-term memory neural network. P TH = P base +

[0078] Among them, P TH For the updated power threshold, P base Based on the threshold, This is the dynamic threshold compensation factor.

[0079] The above embodiments only monitor the transmitted signal of the client terminal device 30. If only the transmitted signal of the client terminal device 30 is monitored, the received signal of the electronically scanned antenna 10 may be too strong, causing the coupling signal strength to exceed the decision threshold, leading to misjudgment by the system. To prevent misjudgment, such as... Figures 13 to 17 As shown in the embodiment of the present invention, the time-division duplex mobile communication system may further include a second directional coupler 250. The second directional coupler 250 is connected between the electronically scanned antenna 10 and the M-channel transceiver circuit 240. The second directional coupler 250 is configured to extract a second radio frequency component from the received signal of the electronically scanned antenna 10. The signal generation circuit 230 is configured to generate a switch control signal based on the first radio frequency component and the second radio frequency component. By integrating directional couplers into both the client terminal device 30 and the electronically scanned antenna 10, and simultaneously acquiring the transmit power of the client terminal device 30 and the receive power at the antenna end, bidirectional signal monitoring is achieved, solving the misjudgment problem of unidirectional monitoring in ship scenarios.

[0080] The second directional coupler 250 can be a device with the same structure as the first directional coupler 220. That is, the second directional coupler 250 is also a four-port network, including: an input terminal, a through output terminal, a coupled output terminal, and an isolation terminal. The connection relationship between the second directional coupler 250, the M-channel transceiver circuits 240, and the electronically scanned antenna 10 is as follows: the input terminal of the second directional coupler 250 is connected to the electronically scanned antenna 10, and the through output terminal is connected to the common terminal of the first RF switch K1 in each transceiver circuit 240. Thus, the electronically scanned antenna 10 is connected to the first RF switch K1 through the second directional coupler 250. The coupled output terminal of the second directional coupler 250 is connected to the input terminal of the signal generation circuit 230. By using the second directional coupler 250 on the side of the electronically scanned antenna 10, non-intrusive coupling of the received signal of the electronically scanned antenna 10 is achieved, and a portion of the RF component, namely the second RF component, is coupled out from the received signal of the electronically scanned antenna 10. The second directional coupler 250 is a passive device with a coupling coefficient of 10-30dB and a directivity greater than 30dB. Through its coupling structure (e.g., a four-port network), it extracts a weak second radio frequency component from the received signal on the main signal path of the electronically scanned antenna 10. The coupling power accounts for 1%–10%, and the extracted second radio frequency component is directed to an independent monitoring channel, namely the guiding signal generation circuit 230, while minimizing interference to the main signal path.

[0081] like Figures 13 to 17 As shown, with both a first directional coupler 220 and a second directional coupler 250 present, the signal generation circuit 230 includes a first preprocessing sub-circuit 231, a second preprocessing sub-circuit 233, and a generation sub-circuit 232. The coupling output of the first directional coupler 220 is connected to the input of the first preprocessing sub-circuit 231, the coupling output of the second directional coupler 250 is connected to the input of the second preprocessing sub-circuit 233, the outputs of the first and second preprocessing sub-circuits 231 and 233 are connected to the input of the generation sub-circuit 232, and the output of the generation sub-circuit 232 is connected to the control terminal of each transceiver circuit 240. That is, the output of the generation sub-circuit 232 is connected to the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The first preprocessing sub-circuit 231 is configured to preprocess the first RF component and then output a first instantaneous level representing the signal strength of the transmitted signal from the client terminal device 30. The second preprocessing subcircuit 233 is configured to preprocess the second radio frequency component and output a second instantaneous level characterizing the signal strength of the received signal from the electronically scanned antenna 10. The generation subcircuit 232 is configured to acquire a threshold signal and generate a switch control signal based on the comparison result of the first instantaneous level, the second instantaneous level, and the threshold signal.

[0082] The first preprocessing subcircuit 231 includes a first standard processing module 2311 and a first power detector 2312. Specifically, it includes a first bandpass filter BPF1, a first low-noise amplifier LNA1, and a first power detector 2312 cascaded sequentially with the coupling output terminal of the first directional coupler 220. The first radio frequency component is sequentially bandpass filtered, amplified, and subjected to low noise before power measurement to obtain a first instantaneous level. The second preprocessing subcircuit 233 includes a second standard processing module 2331 and a second power detector 2332. Specifically, it includes a second bandpass filter BPF2, a second low-noise amplifier LNA2, and a second power detector 2332 cascaded sequentially with the coupling output terminal of the second directional coupler 250. The second radio frequency component is sequentially bandpass filtered, amplified, and subjected to low noise before power measurement to obtain a second instantaneous level. It should be understood that the internal circuit structure of the first preprocessing subcircuit 231 can be referred to the description in the foregoing embodiments, and will not be repeated here for the sake of brevity. The internal circuit structure of the second standard processing module 2331 is the same as or similar to that of the first standard processing module 2311. Therefore, the description of the first standard processing module 2311 in the foregoing embodiments can be referred to. The second power detector 2332 and the first power detector 2312 can be the same type of power detector, such as the same type of RMS power detector. For the sake of brevity, this will not be described in detail here.

[0083] With both the first directional coupler 220 and the second directional coupler 250 present, the generation sub-circuit 232 can also generate a switch control signal via an analog voltage comparator. This is to achieve the generation of the switch control signal via an analog voltage comparator. Figure 13 , Figure 14As shown, in some embodiments where a first directional coupler 220 and a second directional coupler 250 are simultaneously provided, the generation sub-circuit 232 includes: a threshold signal sub-circuit 2321, a first comparator C1, a second comparator C2, and a control signal sub-circuit 2322. The two inputs of the second comparator C2 are connected to the outputs of the first preprocessing sub-circuit 231 and the second preprocessing sub-circuit 233, respectively. The two inputs of the first comparator C1 are connected to the outputs of the first preprocessing sub-circuit 231 and the control signal sub-circuit 2322, respectively. The two inputs of the control signal sub-circuit 2322 are connected to the outputs of the first comparator C1 and the second comparator C2, respectively. The output of the control signal sub-circuit 2322 is connected to the control terminal of the M-channel transceiver circuits 240. That is, the output of the control signal sub-circuit 2322 is connected to the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The threshold signal subcircuit 2321 is configured to generate a threshold level as a threshold signal; the second comparator C2 is configured to output a second level signal based on the comparison result of the first instantaneous level and the second instantaneous level; the first comparator C1 is configured to output a first level signal based on the comparison result of the first instantaneous level and the threshold level; the control signal subcircuit 2322 is configured to output a switch control signal for controlling the target transceiver circuit 240-1 based on the comparison result of the first level signal and the second level signal. It can be understood that the output of the threshold signal subcircuit 2321 is connected to the inverting input of the first comparator C1, the output of the first preprocessing subcircuit 231 is connected to the non-inverting input of the first comparator C1, and the non-inverting and inverting inputs of the second comparator C2 are respectively connected to the outputs of the first preprocessing subcircuit 231 and the second preprocessing subcircuit 233.

[0084] like Figure 13 The control signal subcircuit 2322 can employ a first logic gate circuit. When the generation subcircuit 232 employs a first logic gate circuit, the threshold signal subcircuit 2321 within the generation subcircuit 232 includes: a reference voltage source VREF and an adjustable resistor network AT1. The reference voltage is provided by the reference voltage source VREF. For example, the reference voltage source VREF provides a reference voltage with an accuracy of ±0.1%. The adjustable resistor network AT1 is connected between the output of the reference voltage source VREF and the inverting input of the first comparator C1. Based on manual voltage division adjustment of the adjustable resistor network AT1, a manually configured threshold level is output to the first comparator C1, enabling continuous manual adjustment of the threshold level offline.

[0085] like Figure 14The first logic gate circuit can be replaced by processor 239. When processor 239 is used in control signal sub-circuit 2322, the threshold signal sub-circuit 2321 in generation sub-circuit 232 includes a digital-to-analog converter. The input terminal of the digital-to-analog converter is connected to the output pin of processor 239, and the output terminal of the digital-to-analog converter is connected to the inverting input terminal of the first comparator C1. Processor 239 provides a configuration interface for online configuration of threshold power. The online configuration of threshold voltage can be realized through any configuration interface of serial port and / or network port. After the digital-to-analog converter performs analog-to-digital conversion on the power threshold transmitted from processor 239, it outputs an analog threshold level to the first comparator C1.

[0086] In other embodiments, the generation sub-circuit 232 can generate a switch control signal via digital comparison. For example... Figure 15 As shown, to generate switch control signals through digital comparison, the generation sub-circuit 232 includes a first analog-to-digital converter (ADC1), a second analog-to-digital converter (ADC2), and a processor 239. The input terminal of the first ADC1 is connected to the output terminal of the first preprocessing sub-circuit 231, and the input terminal of the second ADC2 is connected to the output terminal of the second preprocessing sub-circuit 233. The two input pins of the processor 239 are connected to the output terminals of the first ADC1 and the second ADC2, respectively. The output pin of the processor 239 is connected to the control terminal of the M-channel transceiver circuit 240, that is, the output pin of the processor 239 is connected to the control terminal of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The first ADC1 is configured to: perform analog-to-digital conversion on a first instantaneous level and output a first instantaneous power; the second ADC2 performs analog-to-digital conversion on a second instantaneous level and output a second instantaneous power; both the first instantaneous power and the second instantaneous power are digital signals. The processor 239 is configured to: after acquiring the power threshold as a threshold signal, generate a switching control signal based on the comparison result of the first instantaneous power, the second instantaneous power and the power threshold.

[0087] It is understandable that, such as Figure 15As shown, processor 239 is configured to: generate a first switch control signal when the first instantaneous power is greater than a power threshold and the first instantaneous power is greater than a second instantaneous power, to control the target transceiver circuit 240-1 to switch from a receiving state to a transmitting state; otherwise, generate a second switch control signal to control the target transceiver circuit 240-1 to switch from a transmitting state back to a receiving state. In some embodiments, a hysteresis threshold is introduced when processor 239 generates the first switch control signal; that is, the first switch control signal is generated when the first instantaneous power is greater than the sum of the power threshold and the pre-hysteresis threshold, and the first instantaneous power is greater than the second instantaneous power; otherwise, the second switch control signal is generated. For example, the hysteresis threshold is 0.5 dB.

[0088] The raw instantaneous power samplesd by the first analog-to-digital converter (ADC1) and the second analog-to-digital converter (ADC2) fluctuate significantly, exhibiting instantaneous fluctuations. Therefore, in some embodiments, the processor 239 is further configured to: perform average filtering on the raw power sampling data sampled by the first ADC1 using a sliding window average filtering algorithm, with the smoothed average power serving as the first instantaneous power; and perform average filtering on the raw power sampling data sampled by the second ADC2 using the same sliding window average filtering algorithm, with the smoothed average power serving as the second instantaneous power. This eliminates the impact of instantaneous fluctuations in the received signal of the electronically scanned antenna 10 and the transmitted signal of the client terminal equipment 30. The size of the sliding window is adjusted according to actual needs.

[0089] It is understood that the output pins of processor 239 are connected to the control terminals of the M-channel transceiver circuits 240 as follows: they are connected to the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The generated first switch control signal controls the first RF switch K1 and the second RF switch K2 to turn on the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, so that the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1 is connected to the corresponding antenna sector 110 and the client terminal device 30, thereby putting the target transceiver circuit 240 into a transmit state. The generated second switch control signal controls the first RF switch K1 and the second RF switch K2 to turn on the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1, so that the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1 is connected to the corresponding antenna sector 110 and the client terminal device 30, thereby putting the target transceiver circuit 240 into a receive state.

[0090] like Figure 16 and Figure 17As shown, in some embodiments, the internal circuit structure of the second preprocessing sub-circuit 233 and the first preprocessing sub-circuit 231 may be the same: the first standard processing module 2311 in the first preprocessing sub-circuit 231 further includes a first gain adjustment sub-circuit, which is cascaded before the first power detector 2312. The first gain adjustment sub-circuit is configured to adjust the gain of the RF signal processed by the first low-noise amplifier LNA1 and the first bandpass filter BPF1 to the operating range of the first power detector 2312. The second standard processing module 2331 in the second preprocessing sub-circuit 233 further includes a second gain adjustment sub-circuit, which is cascaded before the second power detector 2332. The second gain adjustment sub-circuit is configured to adjust the gain of the RF signal processed by the second low-noise amplifier LNA2 and the second bandpass filter BPF2 to the operating range of the second power detector 2332.

[0091] like Figure 16 As shown, the second gain adjustment sub-circuit can employ an automatic gain control circuit (AGC2). Further implementation details can be found in the description of the first gain adjustment sub-circuit in the preceding embodiments. Figure 17 As shown, the second gain adjustment sub-circuit can be an amplifier array BLNA3, BLNA4 composed of multi-stage bypassable low-noise amplifiers. More implementation details can be found in the description of the first gain adjustment sub-circuit in the foregoing embodiments.

[0092] like Figure 18 As shown, when the generation sub-circuit 232 uses a processor 239, the processor 239 in the generation sub-circuit 232 can also be connected to the mobile communication module 310 of the client terminal device 30. The processor 239 is also configured to: obtain multi-dimensional quality parameters of the radio frequency signals received by the mobile communication module 310 from the client terminal device 30, and process the multi-dimensional quality parameters using a threshold generation strategy that matches the scenario of the time-division duplex mobile communication system to obtain a power threshold. Thus, the power threshold is dynamically and adaptively updated according to the scenario. It should be understood that more implementation details of dynamically updating the power threshold based on the multi-dimensional quality parameters can be found in the description of the aforementioned generation sub-circuit 232, which will not be repeated here for the sake of brevity.

[0093] In the signal generation circuit 230 used to generate the switch control signal, the first power detector 2312 and the second power detector 2332, as key power monitoring devices, have inherent limitations in their characteristics. According to radio frequency measurement standards (IEEE 802.11ah, 3GPP TS 38.104), the dynamic range of the transmit power of the mobile communication module 310 (e.g., a 5G module) of the client terminal equipment 30 typically covers -30dBm to +30dBm (Sub-6 GHz band) or -20dBm to +40dBm (millimeter wave band). However, the operating range of RMS power detectors (such as diode-based analog detection circuits) is generally limited by the nonlinear characteristics of their internal components, covering only -20dBm to +15dBm. This gap directly leads to the following: when the transmit power is lower than the lower boundary power of the RMS power detector, the RMS power detector cannot measure accurately, causing a power control closed-loop failure; when the transmit power exceeds the upper boundary power of the detector, the RMS power detector output is distorted and cannot provide a reliable overload alarm; the instantaneous power fluctuation of the mobile communication module 310 may span a dynamic range of 40 dB, which a single RMS power detector cannot meet. To address this problem, embodiments of the present invention can also employ a power allocation mechanism to expand the strength detection range of the transmitted signal of the client terminal equipment 20 by the first power detector 2312, and the strength detection range of the received signal of the electronically scanned antenna 10 by the second power detector 2332.

[0094] To address the aforementioned issues using a power allocation mechanism, such as... Figure 19 As shown, the signal generation circuit 230 provided in this embodiment of the invention includes: a power divider 236, N preprocessing sub-circuits 234 and 235, and a generation sub-circuit 232. The input terminal of the power divider 236 is connected to the coupling output terminal of the first directional coupler 220. The power divider 236 has N output terminals, which are connected to the input terminals of the N preprocessing sub-circuits 234 and 235 respectively. The output terminals of the N preprocessing sub-circuits 234 and 235 are connected to the input terminal of the generation sub-circuit 232. The output terminal of the generation sub-circuit 232 is connected to the control terminal of each RF switch (first RF switch K1 and second RF switch K2) in the M transceiver circuits 240. The power divider 236 is configured to divide the first radio frequency component into N radio frequency signals; each of the N preprocessing sub-circuits 234 and 235 is configured to preprocess one of the N radio frequency signals and output the corresponding instantaneous level; the generation sub-circuit 232 is configured to acquire a threshold signal and generate a switch control signal based on the comparison result between the N instantaneous levels and the threshold signal.

[0095] like Figure 19As shown, the power divider 236 divides the coupled first RF component into N equal parts. The power of each RF signal output by the power divider 236 is one-Nth of the original power of the first RF component. Here, N = 2, 3, or 4, meaning 2, 3, or 4 power dividers can be used. Each preprocessing subcircuit 234, 235 is equipped with an independent low-noise amplifier LNA3, LNA4, and the gains (G1, G2, ..., G...) of the low-noise amplifiers on different preprocessing subcircuits 234, 235 are... n The amplification factors of the input signals can be different for different preprocessing sub-circuits, so that the output signal power of each preprocessing sub-circuit 234 and 235 is (first RF component / N)×G. i The power detectors on each preprocessing sub-circuit 234 and 235 cover independent power ranges, such as: Channel 1: -30-0 dBm; Channel 2: 0-30 dBm. The combined dynamic range is [-30 dBm, +30 dBm].

[0096] like Figure 19 As shown, in some embodiments, the generation sub-circuit 232 includes: N third comparators C3, C4, a second logic gate circuit 2323, and a threshold signal sub-circuit 2321. The non-inverting input of each third comparator C3, C4 is connected to the output of one of the preprocessing sub-circuits 234, 235, and the inverting input of each third comparator C3, C4 is connected to the output of the threshold signal sub-circuit 2321. The threshold signal sub-circuit 2321 is configured to generate a threshold level. The threshold signal sub-circuit 2321 can be a cascaded reference voltage source VREF and an adjustable resistor network AT1. The adjustable resistor network AT1 outputs a suitable threshold level to each third comparator C3, C4 based on the reference reference voltage provided by the reference voltage source VREF by manually adjusting the voltage divider of the adjustable resistor network AT1. See also... Figure 7As shown, the threshold signal sub-circuit 2321 can also be a cascade of the processor 239, the digital-to-analog converter (DAC), and the buffer. Each third comparator C3, C4 is used to compare the instantaneous level of the output of one of the preprocessing sub-circuits with the threshold level. The second logic gate circuit 2323 is an OR gate, configured to: when any instantaneous level in the comparison results of the N third comparators C3, C4 is greater than the threshold level, output a high-level signal to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to turn on the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 enters the transmit state; otherwise, output a low-level signal to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to turn on the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 enters the receive state.

[0097] like Figure 19 As shown, taking power divider 236 as an example of a two-way power divider, two preprocessing sub-circuits are required: a third preprocessing sub-circuit 234 and a fourth preprocessing sub-circuit 235. The input terminal of power divider 236 is connected to the coupling output terminal of the first directional coupler 220. The two output terminals of power divider 236 are connected to the input terminals of the third preprocessing sub-circuit 234 and the fourth preprocessing sub-circuit 235, respectively. The output terminals of the third preprocessing sub-circuit 234 and the fourth preprocessing sub-circuit 235 are connected to the non-inverting input terminals of the two third comparators C3 and C4, respectively. The inverting input terminals of the two third comparators C3 and C4 are both connected to the output terminal of the threshold signal sub-circuit 2321. The output terminals of the two third comparators C3 and C4 are connected to the input terminal of the second logic gate circuit 2323. The output terminal of the second logic gate circuit 2323 is connected to the control terminals of the first RF switch K1 and the second RF switch K2 in the M-channel transceiver circuit. The power divider 236 is configured to divide the first radio frequency component into a first radio frequency signal and a second radio frequency signal. The third preprocessing sub-circuit 234 preprocesses the first radio frequency signal and outputs a third instantaneous level. The fourth preprocessing sub-circuit 235 preprocesses the second radio frequency signal and outputs a fourth instantaneous level. A third comparator C3 compares the third instantaneous level with a threshold level, and another third comparator C4 compares the fourth instantaneous level with a threshold level. The second logic gate 2323 is configured to output a high-level signal when either the third instantaneous level or the fourth instantaneous level is greater than the threshold level, to control the target transceiver circuit 240-1 to switch from the receiving state to the transmitting state; otherwise, it outputs a low-level signal to control the target transceiver circuit 240-1 to switch back from the transmitting state to the receiving state.

[0098] It should be noted that the internal circuit structures of the N-channel preprocessing subcircuits 234 and 235 in the generation subcircuit 232 can be identical, both consisting of a low-noise amplifier, a bandpass filter, and an RMS power detector cascaded together. The cascading order of the low-noise amplifier and the bandpass filter before the RMS power detector is not limited. For example... Figure 19 As shown, the third preprocessing sub-circuit consists of a low-noise amplifier (LNA3), a bandpass filter (BPF3), and an RMS power detector cascaded together. The fourth preprocessing sub-circuit consists of a low-noise amplifier (LNA4), a bandpass filter (BPF4), and another RMS power detector cascaded together.

[0099] It should be understood that the second logic gate 2323 can be replaced by a cascaded analog-to-digital converter and a programmable logic device, implemented by directly writing Hardware Description Language (HDL) code. The programmable logic device can be a Field-Programmable Gate Array (FPGA) or a Complex Programmable Logic Device (CPLD).

[0100] like Figure 20As shown, in some embodiments, the signal generation circuit 230 includes a first radio frequency front-end module (RF FEM) 236, an RF transceiver 237, and a processor 239. The coupling output of the first directional coupler 220 is connected to the input pin of the processor 239 via the first RF FEM 236 and the RF transceiver 237 in sequence: the input of the first RF FEM 236 is connected to the coupling output of the first directional coupler 220, the output of the first RF FEM 236 is connected to the RF port of the RF transceiver 237, and the digital port of the RF transceiver 237 is connected to the input pin of the processor 239. The output pin of the processor 239 is connected to the control terminal of each transceiver circuit 240; that is, the output pin of the processor 239 is connected to the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240. The first RF FEM 236 is configured to output a first RF signal after standardizing the first RF component. The radio frequency transceiver 237 is configured to sample the first radio frequency signal and output a first data stream. The processor 239 is configured to: extract signal features from the first data stream to obtain a first instantaneous power, and generate a switch control signal based on a comparison between the first instantaneous power and a power threshold. It is understood that the generated switch control signal is either a first switch control signal or a second switch control signal. The processor 239 is configured to: generate a first switch control signal when the power is greater than a power threshold or the sum of the power threshold and the hysteresis return threshold in the first instantaneous moment, to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to be in the state of conducting the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the receive state to the transmit state; and generate a second switch control signal when the power is less than or equal to the power threshold in the first instantaneous moment, to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to be in the state of conducting the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the transmit state back to the receive state.

[0101] The standardization processing performed on the first RF component by the first RF front-end module 236 includes gain adjustment, filtering, and impedance matching, ensuring that the RF signal output by the first RF front-end module 236 meets the input requirements of the RF transceiver 237. The first RF front-end module 236 is a highly integrated module, employing a multi-stage amplification and filtering architecture. The technical specifications of the first RF front-end module 236 are as follows: gain flatness ±0.3 dB, noise figure ≤1.2 dB, and linearity IP3 ≥35 dBm.

[0102] The technical specifications of the RF transceiver 237 are as follows: Sampling rate: ≥2 GS / s, to meet the Nyquist sampling requirements of 200 MHz bandwidth signals; Signal-to-noise ratio: ≥80 dB, effectively suppressing noise interference and ensuring the clear identifiability of RF signals in complex noisy environments; Clock jitter: ≤100 fs, enabling precise control of sampling timing and ensuring the timing accuracy of high-speed data acquisition; Data throughput: ≥10 Gbps, efficiently transmitting the acquired RF digital data stream to meet the real-time processing requirements of high-frequency signals. The real-time data acquisition capability of the RF transceiver 237 achieves microsecond-level response to 30 GHz transmit power from customer terminal equipment, and its low latency ensures the system's rapid response to power fluctuations.

[0103] In some embodiments, the signal features extracted by the processor 239 from the first data stream further include at least one of a first power spectral density and a first power fluctuation rate. The processor 239 is also configured to: perform a fast Fourier transform on the first data stream to obtain a first power spectrum, analyze the first power spectrum to obtain a first power spectral density, and solve for the first power fluctuation rate in the time domain from the first radio frequency data. Based on the first power spectral density, the first instantaneous power, and the first power fluctuation rate, it is determined whether there is an anomaly in the transmitted signal power of the client terminal device 30 (e.g., whether there is a power surge, interference event, etc.). If an anomaly is found, a control signal is generated for the client terminal device 30 to control the power amplifier in the client terminal device 30, thereby adjusting the transmitted power of the client terminal device 30. Specifically, if the first instantaneous power is less than a preset minimum acceptable value, a control signal is generated for the client terminal device 30 to control the power amplifier in the client terminal device 30, thereby increasing the transmitted power of the client terminal device 30.

[0104] like Figure 21 As shown, processor 239 can also be connected to the mobile communication module 310 of client terminal device 30. Processor 239 is further configured to: obtain multi-dimensional quality parameters of the radio frequency signals received by mobile communication module 310 from client terminal device 30, and process the multi-dimensional quality parameters using a threshold generation strategy matching the scenario of the time-division duplex mobile communication system to obtain a power threshold. More implementation details of dynamically generating the power threshold based on the multi-dimensional quality parameters can be found in the description of the aforementioned generation sub-circuit 232, which will not be repeated here for the sake of brevity.

[0105] like Figure 22As shown, in some embodiments, the signal generation circuit 230 may include: a first RF front-end module 236, a second RF front-end module 238, an RF transceiver 237, and a processor 239. The coupling output of the first directional coupler 220 is connected to an RF port of the RF transceiver 237 via the first RF front-end module 236. The coupling output of the second directional coupler 250 is connected to another RF port of the RF receiver via the second RF front-end module 238. The digital port of the RF transceiver 237 is connected to the input pin of the processor 239. The output pin of the processor 239 is connected to the control terminal of each transceiver circuit 240, that is, the control terminals of the first RF switch K1 and the second RF switch K2 in each transceiver circuit 240 are connected.

[0106] The first RF front-end module 236 is configured to: standardize a first RF component and output a first RF signal; the second RF front-end module 238 is configured to standardize a second RF component and output a second RF signal; the RF transceiver 237 is configured to sample the first RF signal and output a first data stream, and sample the second RF signal and output a second data stream. The processor 239 is configured to: extract signal features from the first data stream to obtain a first instantaneous power, and extract signal features from the second data stream to obtain a second instantaneous power, and generate a switching control signal based on a comparison of the first instantaneous power, the second instantaneous power, and a power threshold. The processor 239 is configured to: if the first instantaneous power is greater than a power threshold, or greater than the sum of the power threshold and the hysteresis return threshold, and if the first instantaneous power is greater than a second instantaneous power, generate a first switch control signal to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to be in the state of conducting the transmit enhancement sub-circuit 242 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the receive state to the transmit state; if the first instantaneous power is less than or equal to the power threshold, or the first instantaneous power is not greater than the second instantaneous power, generate a second switch control signal to control the first RF switch K1 and the second RF switch K2 in the target transceiver circuit 240-1 to be in the state of conducting the receive enhancement sub-circuit 241 in the target transceiver circuit 240-1, so that the target transceiver circuit 240-1 switches from the transmit state back to the receive state.

[0107] In some embodiments, the signal features extracted from the first data stream may further include at least one of a first power spectral density and a first power fluctuation rate, and the signal features extracted from the second data stream may further include at least one of a second power spectral density and a second power fluctuation rate. The processor 239 is further configured to: perform a Fast Fourier Transform on the first data stream to obtain a first power spectrum, then analyze the first power spectrum to obtain a first power spectral density; perform a Fast Fourier Transform on the second data stream to obtain a second power spectrum, then analyze the second power spectrum to obtain a second power spectral density. The second power fluctuation rate and the first power fluctuation rate are solved in the time domain from the first radio frequency data and the second radio frequency data. Based on the first instantaneous power, the first power spectrum, and the first power fluctuation rate, it is determined whether there is an anomaly in the transmitted signal power of the client terminal device 30, such as a power surge or the presence of an interference event. If an anomaly is found, a third control signal is generated for the client terminal device 30 to control the power amplifier in the client terminal device 30, thereby adjusting the power of the transmitted signal of the client terminal device 30.

[0108] like Figure 23 As shown, processor 239 can also be connected to the mobile communication module 310 of client terminal device 30. Processor 239 is further configured to: obtain multi-dimensional quality parameters of the radio frequency signals received by mobile communication module 310 from client terminal device 30, and process the multi-dimensional quality parameters using a threshold generation strategy matching the scenario of the time-division duplex mobile communication system to obtain a power threshold. More implementation details of dynamically generating the power threshold based on the multi-dimensional quality parameters can be found in the description of the aforementioned generation sub-circuit 232, which will not be repeated here for the sake of brevity.

[0109] It is understood that the processor 239 in any embodiment of the present invention may be a system-on-a-chip or a programmable logic device.

[0110] The time-division duplex mobile communication system provided in this invention, through the cooperation of the first directional coupler and signal generation circuit at the client terminal device, can generate high-quality transmit / receive switching control signals, eliminating the need for external modules to provide switching control signals and replacing the circulator solution. This achieves a precise transmit / receive isolation mechanism, improving the transmit / receive isolation performance of TDD signal processing in shipboard environments, avoiding signal crosstalk, and increasing signal amplification efficiency by 20-30%. It also shortens the development cycle, eliminates the need for additional switching signal sources, significantly simplifies the system architecture, and reduces the number of hardware components. The time-division duplex mobile communication system provided in this invention is suitable for various ship platforms (such as ocean-going fishing vessels, maritime patrol vessels, and container ships) and different communication scenarios (such as 5G NR, 4G LTE, etc.), especially performing excellently in high-interference areas such as ports. In the dynamic environment of a ship, the time-division duplex mobile communication system provided in this invention can effectively reduce signal interruptions during TDD signal amplification. By real-time monitoring and adaptive adjustment of the transmitted signals of the client terminal device, the stability of communication quality during ship navigation can be improved, meeting the requirements of shipboard high-performance internet systems for continuous, high-quality communication.

[0111] The above description is merely an embodiment of the present invention and is not intended to limit the invention. Various modifications and variations can be made to the present invention by those skilled in the art. Any modifications, equivalent substitutions, improvements, etc., made within the spirit and principles of the present invention should be included within the scope of the claims of the present invention.

Claims

1. A time-division duplex mobile communication system, characterized in that, include: Electronically scanned antennas, radio frequency control devices, and customer terminal equipment; The electronically scanned antenna includes M antenna sectors, where M is a positive integer; The radio frequency control device includes a gating control circuit, a first directional coupler, a signal generation circuit, and M transceiver circuits corresponding to the M antenna sectors. The gating control circuit is configured to monitor the signal quality of the radio frequency signals on the M transceiver circuits, and select a target transceiver circuit from the M transceiver circuits to connect to the client terminal equipment based on the signal quality of the radio frequency signals on the M transceiver circuits. The first directional coupler is connected between the M-channel transceiver circuit and the client terminal device, and the first directional coupler is configured to extract a first radio frequency component from the transmitted signal of the client terminal device. The signal generation circuit is configured to generate a switch control signal based on the first radio frequency component, for controlling the target transceiver circuit to switch between a transmit state and a receive state.

2. The time-division duplex mobile communication system as described in claim 1, characterized in that, Also includes: A second directional coupler is connected between the electronically scanned antenna and the M-channel transceiver circuit. The second directional coupler is configured to extract a second radio frequency component from the received signal of the electronically scanned antenna. The signal generation circuit is configured to generate the switch control signal based on the first radio frequency component and the second radio frequency component.

3. The time-division duplex mobile communication system as described in claim 1, characterized in that, The signal generation circuit includes: The first preprocessing sub-circuit is configured to preprocess the first radio frequency component and then output a first instantaneous level characterizing the signal strength of the transmitted signal; A sub-circuit is configured to acquire a threshold signal and generate the switch control signal based on a comparison between the first instantaneous level and the threshold signal.

4. The time-division duplex mobile communication system as described in claim 3, characterized in that, The generating sub-circuit includes: A threshold signal sub-circuit is configured to generate a threshold level as the threshold signal; A first comparator has two input terminals connected to the output terminals of the first preprocessing sub-circuit and the threshold signal sub-circuit, respectively. The output terminal of the first comparator is connected to the control terminal of the M-channel transceiver circuit. The first comparator is configured to: output a high-level signal when the first instantaneous level is greater than the threshold level, to control the target channel transceiver circuit to switch from the receiving state to the transmitting state; and output a low-level signal when the first instantaneous level is less than or equal to the threshold level, to control the target channel transceiver circuit to switch back from the transmitting state to the receiving state.

5. The time-division duplex mobile communication system as described in claim 3, characterized in that, The generating sub-circuit includes: The first analog-to-digital converter has its input terminal connected to the output terminal of the first preprocessing sub-circuit. The first analog-to-digital converter is configured to perform analog-to-digital conversion on the first instantaneous level output by the first preprocessing sub-circuit and then output a first instantaneous power. The processor has an input pin connected to the output of the first analog-to-digital converter and an output pin connected to the control terminal of the M-channel transceiver circuit. The processor is configured to: acquire a power threshold as the threshold signal; when the first instantaneous power is greater than the power threshold, output a first switch control signal to control the target channel transceiver circuit to switch from the receiving state to the transmitting state; and when the first instantaneous power is less than or equal to the power threshold, output a second switch control signal to control the target channel transceiver circuit to switch from the transmitting state back to the receiving state.

6. The time-division duplex mobile communication system as described in claim 2, characterized in that, The signal generation circuit includes: The first preprocessing sub-circuit is configured to preprocess the first radio frequency component and then output a first instantaneous level characterizing the signal strength of the transmitted signal; The second preprocessing sub-circuit is configured to preprocess the second radio frequency component and then output a second instantaneous level characterizing the signal strength of the received signal. A sub-circuit is configured to acquire a threshold signal and generate the switch control signal based on a comparison of the first instantaneous level, the second instantaneous level, and the threshold signal.

7. The time-division duplex mobile communication system as described in claim 6, characterized in that, The generating sub-circuit includes: A threshold signal subcircuit is configured to generate a threshold level as the threshold signal; The first comparator has two input terminals connected to the output terminal of the first preprocessing sub-circuit and the output terminal of the threshold signal sub-circuit, respectively. The first comparator is configured to output a first level signal based on the comparison result between the first instantaneous level and the threshold level. The second comparator has two input terminals connected to the output terminals of the first preprocessing sub-circuit and the second preprocessing sub-circuit, respectively. The second comparator is configured to output a second level signal based on the comparison result between the first instantaneous level and the second instantaneous level. The control signal sub-circuit has two input terminals connected to the output terminals of the first comparator and the second comparator, respectively. The output terminal of the control signal sub-circuit is connected to the control terminal of the M-channel transceiver circuit. The control signal sub-circuit is configured to output the switch control signal based on the comparison result of the first level signal and the second level signal.

8. The time-division duplex mobile communication system as described in claim 6, characterized in that, The generating sub-circuit includes: The first analog-to-digital converter has its input terminal connected to the output terminal of the first preprocessing sub-circuit. The first analog-to-digital converter is configured to perform analog-to-digital conversion on the first instantaneous level and then output the first instantaneous power. The second analog-to-digital converter has its input terminal connected to the output terminal of the second preprocessing sub-circuit. The second analog-to-digital converter performs analog-to-digital conversion on the second instantaneous level and outputs the second instantaneous power. The processor has input pins connected to the outputs of the first analog-to-digital converter and the second analog-to-digital converter, and output pins connected to the control terminal of the M-channel transceiver circuit. The processor is configured to: acquire a power threshold as the threshold signal; when the first instantaneous power is greater than the power threshold and the first instantaneous power is greater than the second instantaneous power, output a first switch control signal to control the target channel transceiver circuit to switch from the receiving state to the transmitting state; otherwise, generate a second switch control signal to control the target channel transceiver circuit to switch from the transmitting state back to the receiving state.

9. The time-division duplex mobile communication system as described in claim 6, characterized in that: The first preprocessing sub-circuit includes: a first bandpass filter, a first low-noise amplifier, and a first power detector, which are cascaded sequentially with the coupling output terminal of the first directional coupler; The second preprocessing sub-circuit includes: a second bandpass filter, a second low-noise amplifier, and a second power detector, which are cascaded sequentially with the coupling output terminal of the second directional coupler.

10. The time-division duplex mobile communication system as described in claim 9, characterized in that: The first preprocessing sub-circuit further includes: a first gain adjustment sub-circuit, cascaded before the first power detector, wherein the first gain adjustment sub-circuit is configured to: adjust the gain of the radio frequency signal processed by the first low noise amplifier and the first bandpass filter to the operating range of the first power detector. The second preprocessing sub-circuit further includes a second gain adjustment sub-circuit, cascaded before the second power detector, wherein the second gain adjustment sub-circuit is configured to adjust the gain of the radio frequency signal processed by the second low-noise amplifier and the second bandpass filter to the operating range of the second power detector.

11. The time-division duplex mobile communication system as described in claim 1, characterized in that, The signal generation circuit includes: The power divider is configured to divide the first radio frequency component into N radio frequency signals; N preprocessing sub-circuits, each of which is configured to preprocess one of the N radio frequency signals and then output the corresponding instantaneous level. A generation sub-circuit is configured to acquire a threshold signal and generate the switch control signal based on the comparison result between the N instantaneous levels output by the N preprocessing sub-circuits and the threshold signal.

12. The time-division duplex mobile communication system as described in claim 1, characterized in that, The signal generation circuit includes: A first radio frequency front-end module is connected to the coupling output terminal of the first directional coupler. The first radio frequency front-end module is configured to output a first radio frequency signal after standardizing the first radio frequency component. An RF transceiver is connected to the first RF front-end module, and the RF transceiver is configured to sample the first RF signal and output a first data stream. A processor, connected to the radio frequency transceiver, is configured to: extract signal features from the first data stream to obtain a first instantaneous power, and generate the switching control signal based on a comparison between the first instantaneous power and a power threshold.

13. The time-division duplex mobile communication system as described in claim 2, characterized in that, The signal generation circuit includes: A first radio frequency front-end module is connected to the coupling output terminal of the first directional coupler. The first radio frequency front-end module is configured to output a first radio frequency signal after standardizing the first radio frequency component. The second radio frequency front-end module is connected to the coupling output terminal of the second directional coupler. The second radio frequency front-end module is configured to output the second radio frequency signal after standardizing the second radio frequency component. An RF transceiver is connected to the first RF front-end module and the second RF front-end module. The RF transceiver is configured to: sample the first RF signal and output a first data stream, and sample the second RF signal and output a second data stream. A processor, connected to the radio frequency transceiver, is configured to: extract signal features from the first data stream to obtain a first instantaneous power; extract signal features from the second data stream to obtain a second instantaneous power; and generate the switch control signal based on a comparison of the first instantaneous power, the second instantaneous power, and a power threshold.

14. The time-division duplex mobile communication system as described in any one of claims 5, 8, 12, and 13, characterized in that, The processor is also connected to the mobile communication module of the client terminal device; The processor is further configured to: obtain multi-dimensional quality parameters characterizing the received signal quality of the mobile communication module from the client terminal device, and process the multi-dimensional quality parameters using a threshold generation strategy that matches the scenario in which the time-division duplex mobile communication system is located, so as to obtain the power threshold.

15. The time-division duplex mobile communication system as described in claim 14, characterized in that, The processor is configured to: The system obtains multi-dimensional quality parameters characterizing the received signal quality of the mobile communication module and scene status information of the time-division duplex mobile communication system from the client terminal device. Key features are extracted from the multidimensional quality parameters and the scene state information; The extracted key features are input into a long short-term memory neural network for prediction, so as to output a dynamic threshold compensation factor. The power threshold is obtained based on the dynamic threshold compensation factor and the basic threshold.

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