Horizontal omnidirectional transmitting array antenna and wireless communication system

Abstract

The application discloses a horizontal omnidirectional transmission array antenna and a wireless communication system, and relates to the technical field of antennas.The antenna comprises a feed source, a transmission array, a first beam-restricting reflector and a second beam-restricting reflector.The transmission array coaxially surrounds and comprises at least two transmission array layers arranged in a stack, and each layer compensates the phase of a quasi-spherical electromagnetic wave generated by the feed source to convert the quasi-spherical electromagnetic wave into a horizontal plane uniform plane electromagnetic wave.Two beam-restricting reflectors are arranged on opposite sides of the transmission array and are connected through the transmission array, and are used for collecting the quasi-spherical electromagnetic wave radiated by the feed source to the direction of the beam-restricting reflector and guiding the quasi-spherical electromagnetic wave to the transmission array.The application can solve the problems of low gain, high sidelobe, uneven radiation energy coverage and short transmission distance of the existing plane omnidirectional antenna, and can solve the problems of high sidelobe level, poor azimuth plane non-circularity and narrow bandwidth of the existing transmission array omnidirectional antenna, and can meet the high performance requirements of millimeter wave broadband omnidirectional communication.

Description

Technical Field

[0001] This invention relates to the field of antenna technology, and in particular to a horizontal omnidirectional transmission array antenna and a wireless communication system. Background Technology

[0002] As 5G / 6G mobile communication technologies evolve towards higher frequencies and higher speeds, the millimeter-wave band, with its large bandwidth and high data rate, has become a core research direction for wireless communication systems such as drones, vehicle-to-everything (V2X) networks, and the Internet of Things (IoT). Omnidirectional antennas, as key components for achieving 360-degree coverage without dead zones, require comprehensive performance in the azimuth plane, including high gain, stable omnidirectional radiation, low sidelobe levels, and wideband adaptability, to cope with complex electromagnetic environments and long-distance transmission requirements. Existing millimeter-wave omnidirectional antennas are mainly divided into planar microstrip antennas and transmissive array antennas. While planar omnidirectional antennas are simple in structure and easy to integrate, they suffer from fatal flaws such as low gain, excessively high sidelobes, and energy dispersion. The dispersed radiated energy results in short transmission distances, failing to meet the requirements for high-reliability communication. Although transmissive array omnidirectional antennas improve gain through phase modulation, current technologies still struggle to simultaneously achieve wide bandwidth, low sidelobes, and omnidirectional uniformity. They generally suffer from excessively high sidelobe levels, poor azimuth plane non-circularity, and narrow bandwidth, making it difficult to achieve multi-performance optimization of high gain, low sidelobes, wide bandwidth, and stable omnidirectional radiation. Therefore, developing a compact, high-performance millimeter-wave broadband low-sidelobe omnidirectional transmission array antenna to overcome existing technological bottlenecks is of great significance for promoting the large-scale application of millimeter-wave communication in full coverage. Summary of the Invention

[0003] The main objective of this invention is to propose a horizontal omnidirectional transmission array antenna and a wireless communication system, which aims to solve the problems of low gain, high sidelobes, uneven radiation energy coverage, and short transmission distance of existing planar omnidirectional antennas, as well as the problems of excessively high sidelobe levels, poor azimuth plane non-circularity, and narrow bandwidth of existing transmission array omnidirectional antennas, so as to meet the high performance requirements of millimeter-wave broadband omnidirectional communication.

[0004] To achieve the above objectives, the present invention proposes a horizontal omnidirectional transmission array antenna, comprising: The feed source, arranged along the axis of the horizontal omnidirectional transmission array antenna, is used to receive the input radio frequency excitation signal and generate quasi-spherical electromagnetic waves. A transmission array is coaxially arranged around the feed source. The transmission array includes at least two transmission array layers stacked along the axial direction of the horizontal omnidirectional transmission array antenna. Each transmission array layer includes a circular substrate and a plurality of transceiver units distributed in a circular array on the circular substrate. The transceiver units are used to receive the quasi-spherical electromagnetic wave and perform phase compensation on the quasi-spherical electromagnetic wave to convert the quasi-spherical electromagnetic wave into a horizontal uniform planar electromagnetic wave before radiation. Two beam-constrained reflectors are arranged on opposite sides of the horizontal omnidirectional transmission array antenna along the axis of the antenna. The two beam-constrained reflectors are connected through the transmission array. A feed source is provided between the two beam-constrained reflectors to collect quasi-spherical electromagnetic waves radiated by the feed source toward the beam-constrained reflectors and guide the collected quasi-spherical electromagnetic waves to the transmission array.

[0005] In one embodiment, each of the transceiver units includes: A receiving dipole unit is positioned close to the feed source to receive the quasi-spherical electromagnetic waves; A transmitting dipole unit is positioned away from the feed source to radiate uniform planar electromagnetic waves on the horizontal plane. A delay transmission line is located between the receiving dipole unit and the transmitting dipole unit, and connects the receiving dipole unit and the transmitting dipole unit. The delay transmission line is configured to adjust its physical length to adjust the phase difference between the quasi-spherical electromagnetic wave received by the corresponding receiving dipole unit and the horizontal uniform planar electromagnetic wave radiated by the transmitting dipole unit, thereby changing the phase distribution between different transmission array layers to transform the spherical phase distribution of the quasi-spherical electromagnetic wave into the planar equal phase distribution of the horizontal uniform planar electromagnetic wave.

[0006] In one embodiment, the feed source includes: A monopole radiator is arranged along the axial direction of the horizontal omnidirectional transmission array antenna; The feeding structure has an odd number of transmission array layers. The feeding structure is located in the middle transmission array layer. The output end of the feeding structure is connected to the input end of the monopole radiator to provide a radio frequency excitation signal to the monopole radiator to excite the monopole radiator to generate the quasi-spherical electromagnetic wave.

[0007] In one embodiment, the power supply structure includes: A power supply network is provided on one side of the annular substrate to receive the fed radio frequency excitation signal, divide the radio frequency excitation signal into multiple equal-amplitude and in-phase signals and output them after impedance matching, wherein the number of equal-amplitude and in-phase signals is even. A radiating structure is disposed on the side of the annular substrate away from the feed network. The input end of the radiating structure is connected to the output end of the feed network, and the output end of the radiating structure is connected to the input end of the monopole radiator. It is used to receive the impedance-matched equal-amplitude and in-phase signal and radiate it to the monopole radiator.

[0008] In one embodiment, the power supply network includes: A microstrip power divider has multiple signal output terminals. The microstrip power divider is used to divide the radio frequency excitation signal into multiple equal-amplitude and in-phase signals, and convert the multiple equal-amplitude and in-phase signals into multiple balanced signals. The signal output terminals are used to output a balanced signal. The radiating structure includes multiple bent dipoles; The multiple bent dipoles are arranged at equal intervals along the circumferential direction; The number of the bent dipoles is even, and the multiple bent dipoles are connected one-to-one with the multiple signal output terminals; The bent dipole is used to receive the balance signal and radiate the received balance signal to the monopole radiator.

[0009] In one embodiment, the power supply structure further includes: Multiple matching parasitic units are disposed on the side of the annular substrate away from the power supply network and located on the periphery of the radiating structure. The positions of the multiple matching parasitic units correspond one-to-one with the positions of the multiple bent dipoles. The matching parasitic unit is used to adjust the input impedance of the bent dipole to adjust the impedance matching between the feed source and the feed network, and to smooth the radiation pattern of the bent dipole to compensate for the radiation circularity of the horizontal omnidirectional transmission array antenna in the azimuth plane.

[0010] In one embodiment, at least two transceiver units of the transmission array layer are staggered along the axial direction of the horizontal omnidirectional transmission array antenna to form a plurality of first subarray groups and a plurality of second subarray groups along the axial direction of the horizontal omnidirectional transmission array antenna. The plurality of first subarray groups and the plurality of second subarray groups are alternately arranged circumferentially to compensate for the azimuth pattern non-circularity of the horizontal omnidirectional transmission array antenna caused by the periodic arrangement of the transceiver units.

[0011] In one embodiment, a reference plane is defined that is perpendicular to the horizontal plane along the central axis of the horizontal omnidirectional transmission array antenna and is the transceiver unit of the transceiver array layer. The projections of the transceiver units of the first subarray group and the transceiver units of the second subarray group onto the reference plane have a preset rotation angle.

[0012] In one embodiment, at least one of the beam-constraining reflectors has a reflective surface on the side facing the transmission array, and the reflective surface is a conical surface.

[0013] The present invention also proposes a wireless communication system, including a horizontal omnidirectional transmission array antenna as described above.

[0014] In this invention, a quasi-spherical electromagnetic wave is generated by a feed source arranged along the axial direction of a horizontal omnidirectional transmission array antenna. This feed source, coaxially arranged around the feed source, is used in conjunction with a transmission array. At least two transceiver units in the transmission array layer, stacked along the axial direction of the horizontal omnidirectional transmission array antenna, perform phase compensation on the quasi-spherical electromagnetic wave, converting it into a uniform horizontal planar electromagnetic wave before radiation. This achieves high-gain and stable omnidirectional coverage in the azimuth plane. Furthermore, this invention incorporates two beam-constraining reflectors arranged along the axial direction of the horizontal omnidirectional transmission array antenna on opposite sides of the transmission array. These reflectors guide the quasi-spherical electromagnetic wave radiated from the feed source towards the reflectors into the transmission array. This refocuses the electromagnetic wave, which was originally propagating in the non-operating direction, and allows it to participate in the phase modulation process of the transmission array. This improves the transmission array's efficiency in receiving energy radiated from the feed source and reduces energy loss in the non-operating direction. This configuration allows the horizontal omnidirectional transmission array antenna to maintain a compact structure while leveraging the phase modulation capability of the multi-layer transmission array and the energy convergence effect of the two beam-constrained reflectors to optimize radiation performance. This improves upon the low gain and energy dispersion issues of traditional planar omnidirectional antennas, while also mitigating the shortcomings of existing transmission array omnidirectional antennas such as excessively high sidelobe levels and poor azimuth non-circularity. This approach is beneficial for meeting the comprehensive requirements of millimeter-wave communication systems for broadband, low sidelobe, and stable omnidirectional radiation, and promotes the large-scale application of millimeter-wave communication in full-coverage scenarios. Attached Figure Description

[0015] To more clearly illustrate the technical solutions in the embodiments of the present invention or the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on the structures shown in these drawings without creative effort.

[0016] Figure 1 This is a cross-sectional view of the horizontal omnidirectional transmission array antenna of the present invention; Figure 2 This is a side view of the horizontal omnidirectional transmission array antenna of the present invention; Figure 3 This is a top view of the horizontal omnidirectional transmission array antenna of the present invention; Figure 4 This is a simulation diagram of the electromagnetic field of the horizontal omnidirectional transmission array antenna of the present invention; Figure 5 This is a polar coordinate diagram of the radiation pattern of the horizontal omnidirectional transmission array antenna of the present invention in the vertical plane; Figure 6 This is a polar coordinate diagram of the radiation pattern of the horizontal omnidirectional transmission array antenna of the present invention in the horizontal plane; Figure 7This is a schematic diagram of the transceiver unit of the present invention; Figure 8 This is a graph showing the characteristic curves of amplitude and phase of the transceiver unit as a function of frequency for the horizontal omnidirectional transmission array antenna of the present invention under different delay transmission line lengths. Figure 9 This is a top view of the power supply structure of the present invention; Figure 10 This is a schematic diagram of the structure of the horizontal omnidirectional transmission array antenna of the present invention.

[0017] Explanation of icon numbers: 100. Horizontal omnidirectional transmission array antenna; 10. Feed source; 11. Monopole radiator; 12. Feed structure; 121. Feed network; 122. Radiation structure; 1221. Bent dipole; 123. Matching parasitic element; 20. Transmission array; 21. Transmission array layer; 211. Circular substrate; 212. Transmit / receive unit; 2121. Receiver dipole element; 2122. Transmitter dipole element; 2123. Delay transmission line; l_delay, length of delay transmission line; 21231. Receiver section; 21232. Transmitter section; 21233. Wire conductor; 21201. First subarray group; 21202. Second subarray group; 30. Beam-constrained reflector; 31. Reflector surface; 40. Coaxial connector; 50. Fixing screw; 60. Fixing nut.

[0018] The realization of the objective, functional features and advantages of the present invention will be further explained in conjunction with the embodiments and with reference to the accompanying drawings. Detailed Implementation

[0019] The technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those of ordinary skill in the art without creative effort are within the scope of protection of the present invention.

[0020] As 5G / 6G mobile communication technologies evolve towards higher frequencies and higher speeds, the millimeter-wave band, with its large bandwidth and high data rate, has become a core research direction for wireless communication systems such as drones, vehicle-to-everything (V2X) networks, and the Internet of Things (IoT). Omnidirectional antennas, as key components for achieving 360-degree coverage without dead zones, require comprehensive performance in the azimuth plane, including high gain, stable omnidirectional radiation, low sidelobe levels, and wideband adaptability, to cope with complex electromagnetic environments and long-distance transmission requirements. Existing millimeter-wave omnidirectional antennas are mainly divided into planar microstrip antennas and transmissive array antennas. While planar omnidirectional antennas are simple in structure and easy to integrate, they suffer from fatal flaws such as low gain, excessively high sidelobes, and energy dispersion. The dispersed radiated energy results in short transmission distances, failing to meet the requirements for high-reliability communication. Although transmissive array omnidirectional antennas improve gain through phase modulation, current technologies still struggle to simultaneously achieve wide bandwidth, low sidelobes, and omnidirectional uniformity. They generally suffer from excessively high sidelobe levels, poor azimuth plane non-circularity, and narrow bandwidth, making it difficult to achieve multi-performance optimization of high gain, low sidelobes, wide bandwidth, and stable omnidirectional radiation. Therefore, developing a compact, high-performance millimeter-wave broadband low-sidelobe omnidirectional transmission array antenna to overcome existing technological bottlenecks is of great significance for promoting the large-scale application of millimeter-wave communication in full coverage.

[0021] This invention proposes a horizontal omnidirectional transmission array antenna 100.

[0022] Please see Figures 1 to 3 In one embodiment of the present invention, the horizontal omnidirectional transmission array antenna 100 includes: The feed 10 is arranged along the axis of the horizontal omnidirectional transmission array antenna 100 and is used to receive the input radio frequency excitation signal and generate quasi-spherical electromagnetic waves. The transmission array 20 is coaxially arranged around the feed 10. The transmission array 20 includes at least two transmission array layers 21 stacked along the axial direction of the horizontal omnidirectional transmission array antenna 100. Each transmission array layer 21 includes a circular substrate 211 and a plurality of transceiver units 212 arranged in a circular array on the circular substrate 211. The transceiver units 212 are used to receive quasi-spherical electromagnetic waves and perform phase compensation on the quasi-spherical electromagnetic waves to convert the quasi-spherical electromagnetic waves into horizontal uniform planar electromagnetic waves before radiation. Two beam-constrained reflectors 30 are arranged on opposite sides of the horizontal omnidirectional transmission array antenna 100 along the axis of the transmission array 20. The two beam-constrained reflectors 30 are connected through the transmission array 20. A feed source 10 is provided between the two beam-constrained reflectors 30 to collect quasi-spherical electromagnetic waves radiated by the feed source 10 toward the beam-constrained reflectors 30 and guide the collected quasi-spherical electromagnetic waves to the transmission array 20.

[0023] In this embodiment, the horizontal omnidirectional transmission array antenna 100 further includes a coaxial connector 40, which is used to connect the radio frequency cable to the feed source 10. The feed source 10 is directly powered by the coaxial connector 40 and is used to receive the radio frequency excitation signal input from the external radio frequency cable and generate quasi-spherical electromagnetic waves to feed into the transmission array 20. The feed source 10 is a central metal probe, i.e., a broadband omnidirectional monopole feed source 10. The central metal probe is a standard quarter-wavelength monopole structure with rotationally symmetric current distribution characteristics in the azimuth plane. It can have uniform azimuth plane radiation characteristics before the quasi-spherical electromagnetic waves are transmitted to the transmission array 20, thereby achieving uniform omnidirectional radiation in the azimuth plane and improving the radiation circularity of the horizontal omnidirectional transmission array antenna 100.

[0024] Because existing omnidirectional antennas with transmission arrays generally suffer from problems such as excessively high sidelobe levels, poor azimuth non-circularity, and narrow bandwidth, in order to achieve multi-performance optimization of high gain, low sidelobe, wide bandwidth, and stable omnidirectional radiation, the feed 10 of this embodiment is arranged along the axial direction of the horizontal omnidirectional transmission array antenna 100, and a transmission array 20 is arranged around the outer periphery of the feed 10, with the transmission array 20 arranged coaxially with the feed 10. The transmission array 20 includes at least two transmission array layers 21, which are stacked along the axial direction of the horizontal omnidirectional transmission array antenna 100 to increase the effective aperture of the transmission array 20 and improve the phase modulation degree of freedom, thereby improving the gain and bandwidth characteristics of the horizontal omnidirectional transmission array antenna 100. Since the horizontal omnidirectional transmission array antenna 100 essentially achieves uniform omnidirectional radiation in the azimuth plane, in order to improve the circularity of omnidirectional radiation, the feed 10 at the center of the horizontal omnidirectional transmission array antenna 100 needs to uniformly feed the surrounding transmission arrays 20, while ensuring that the phase shifts of the transceiver units 212 of the same transmission array layer 21 tend to be the same. Based on this, each transmission array layer 21 includes a circular substrate 211 and multiple transceiver units 212. The multiple transceiver units 212 are arranged in a circular array on the corresponding circular substrate 211, that is, each transmission array layer 21 is a symmetrical circular structure. Each transceiver unit 212 is used to receive quasi-spherical electromagnetic waves radiated by the feed 10, perform phase compensation on the received quasi-spherical electromagnetic waves, and convert the phase-compensated quasi-spherical electromagnetic waves into uniform horizontal plane electromagnetic waves before radiating them outward. The feed 10 is located at the center of the horizontal omnidirectional transmission array antenna 100 and radiates quasi-spherical electromagnetic waves outward. A fixed phase shift is introduced inside the peripherally circularly equidistantly arranged transceiver units 212. This fixed phase shift is used to cancel the phase path difference between the feed 10 and each transceiver unit 212, thereby correcting the wavefront of the quasi-spherical electromagnetic waves into uniform horizontal plane electromagnetic waves, which is beneficial to improving the beam pointing accuracy and radiation efficiency of the horizontal omnidirectional transmission array antenna 100.

[0025] The feed 10 is located at the center of the horizontal omnidirectional transmission array antenna 100, rather than being an off-center structure. Furthermore, each transmission array layer 21 uses a circular substrate 211, allowing multiple transceiver units 212 within the same transmission array layer 21 to employ identical structures. With the delay transmission line 2123 of the transceiver units 212 having the same length l_delay, the distance from the feed 10 to each transceiver unit 212 in the same transmission array layer 21 can be the same. This results in a more uniform phase difference between each transceiver unit 212, reducing phase error accumulation and improving the azimuth radiation uniformity of the horizontal omnidirectional transmission array antenna 100. If the feed 10 is not located at the center of the horizontal omnidirectional transmission array antenna 100, then each transceiver unit 212 must have a separately designed delay transmission line 2123 of different lengths to achieve the same phase difference, increasing the design complexity, manufacturing difficulty, and cost of the transmission array 20. Therefore, placing the feed 10 at the center of the horizontal omnidirectional transmission array antenna 100 and using a circular substrate 211 with multiple transceiver units 212 arranged in a circular array on the circular substrate 211 helps to simplify the design and manufacturing process of the transmission array 20, while making the azimuth radiation of the horizontal omnidirectional transmission array antenna 100 more uniform and stable.

[0026] To optimize the radiation performance of the horizontal omnidirectional transmission array antenna 100, beam-constraining reflectors 30 are arranged on opposite sides of the transmission array 20 along the axial direction of the antenna 100. The two beam-constraining reflectors 30 are connected by fixing screws 50 and fixing nuts 60. A feed 10 is provided between the two beam-constraining reflectors 30. The beam-constraining reflectors 30 can guide the quasi-spherical electromagnetic waves radiated from the feed 10 towards the beam-constraining reflectors 30 to the transmission array 20, so that the quasi-spherical electromagnetic waves that originally propagated in the non-operating direction are refocused and participate in the phase modulation process of the transmission array 20, thereby improving the receiving efficiency of the transmission array 20 for the radiated energy from the feed 10, reducing the radiated energy loss of the feed 10 in the non-operating direction, and making the uniform planar electromagnetic waves in the horizontal plane radiated more concentratedly in the horizontal direction. This helps to reduce the sidelobe level of the horizontal omnidirectional transmission array antenna 100 and enhance the main beam gain. Two beam-constrained reflectors 30 are respectively a first beam-constrained reflector disposed on top of the transmission array 20 and a second beam-constrained reflector disposed on bottom of the transmission array 20. In addition to collecting and guiding quasi-spherical electromagnetic waves, the first and second beam-constrained reflectors also serve as structural support components connecting the transmission array 20, enhancing the overall structural stability of the horizontal omnidirectional transmission array antenna 100. A non-radiating region is formed below the second beam-constrained reflector. This non-radiating region facilitates the extension of additional processing structures and feed lines, reserving operational space for the assembly and debugging of the horizontal omnidirectional transmission array antenna 100 without affecting the uniform planar electromagnetic wave radiation performance, thus improving the engineering practicality of the horizontal omnidirectional transmission array antenna 100.

[0027] In this invention, a quasi-spherical electromagnetic wave is generated by a feed 10 arranged along the axial direction of a horizontal omnidirectional transmission array antenna 100. This feed 10, coaxially arranged around the feed 10, utilizes at least two transceiver units 212 stacked along the axial direction of the horizontal omnidirectional transmission array antenna 100 to perform phase compensation on the quasi-spherical electromagnetic wave. This converts the quasi-spherical electromagnetic wave into a uniform planar electromagnetic wave before radiation, thereby achieving high-gain and stable omnidirectional coverage in the azimuth plane. Furthermore, this invention uses two beam-constraining reflectors 30 arranged along the axial direction of the horizontal omnidirectional transmission array antenna 100 on opposite sides of the transmission array 20. The beam-constraining reflectors 30 guide the quasi-spherical electromagnetic wave radiated from the feed 10 towards the beam-constraining reflectors 30 to the transmission array 20. This causes the electromagnetic wave, originally propagating in the non-operating direction, to be refocused and participate in the phase modulation process of the transmission array 20, improving the receiving efficiency of the transmission array 20 for the radiated energy from the feed 10 and reducing the radiated energy loss of the feed 10 in the non-operating direction. This configuration allows the horizontal omnidirectional transmission array antenna 100 to maintain a compact structure while leveraging the phase modulation capability of the multi-layer transmission array 20 layers and the energy convergence effect of the two beam-constrained reflectors 30 to synergistically optimize radiation performance. This improves upon the low gain and energy dispersion issues of traditional planar omnidirectional antennas, while also mitigating the shortcomings of existing omnidirectional antennas with 20-layer transmission arrays, such as excessively high sidelobe levels and poor azimuth non-circularity. This approach is beneficial for meeting the comprehensive requirements of millimeter-wave communication systems for broadband, low sidelobe, and stable omnidirectional radiation, and promotes the large-scale application of millimeter-wave communication in full-coverage scenarios.

[0028] like Figure 4 As shown in the figure, this is a simulated electric field distribution diagram of the horizontal omnidirectional transmission array antenna 100. A color gradient from 0 to 6152 V / m is used to visually display the propagation and field distribution characteristics of quasi-spherical electromagnetic waves within the structure of the horizontal omnidirectional transmission array antenna 100. The electric field is strongest at feed 10, presenting a reddish-yellow region and forming a distinct standing wave and energy concentration area. The left and right sides of feed 10 are the radiation or transmission regions of the transmission array 20, where the electric field gradually attenuates and tends to become uniform. The dashed lines in the figure divide the electric field region into three areas: the left area is the quasi-spherical electromagnetic wave region, with a divergent or converging field distribution that approximates a spherical wavefront; the middle area is the transmission array 20 region, i.e., the strongly coupled resonant region; and the right area is the horizontally uniform planar electromagnetic wave region, with a regular field strength distribution and parallel equiphase surfaces, conforming to the far-field planar wave characteristics. The overall data reflects the physical process of the quasi-spherical electromagnetic wave transitioning from near-field non-uniform excitation to far-field uniform plane wave after modulation by the transmission array 20. It verifies the effectiveness of the transceiver unit 212 in the transmission array 20 in performing phase compensation on the quasi-spherical electromagnetic wave and converting it into a horizontal plane uniform electromagnetic wave. This shows that the horizontal omnidirectional transmission array antenna 100 can achieve the expected beamforming and energy conversion functions.

[0029] like Figure 5 As shown, this figure is a polar coordinate diagram of the radiation pattern of the horizontal omnidirectional transmission array antenna 100 in the vertical plane, displaying the vertical plane radiation characteristics of the horizontal omnidirectional transmission array antenna 100 at three frequency points: 24 GHz, 28 GHz, and 32 GHz, compared with the simulation. Solid lines represent simulation results, while dotted or dashed lines represent measured data. Different colors correspond to different frequencies: 24 GHz corresponds to black or blue, 28 GHz to green or purple, and 32 GHz to orange or red. The results show that the co-polarization radiation patterns at each frequency point exhibit a typical double-lobed or eight-lobed symmetrical structure, with the main lobe pointing approximately ±60 degrees and ±120 degrees, respectively. The simulation and measurement results are highly consistent, verifying the accuracy of the simulated vertical plane radiation pattern of the horizontal omnidirectional transmission array antenna 100. The cross-polarization level is generally more than 20 dB lower than the co-polarization level, and in most areas, it is below -25 dB, indicating that the horizontal omnidirectional transmission array antenna 100 has good polarization purity and isolation performance. Meanwhile, as the frequency increases from 24GHz to 32GHz, the main lobe narrows slightly and the side lobe level increases slightly, which is consistent with the trend of enhanced directivity caused by the increase in electrical size at high frequencies. Overall, this reflects that the horizontal omnidirectional transmission array antenna 100 has stable broadband radiation characteristics and reliable engineering implementation consistency in the K-band.

[0030] like Figure 6 As shown, this figure is a polar coordinate plot of the radiation pattern of the horizontal omnidirectional transmission array antenna 100 in the horizontal plane, displaying the measured and simulated horizontal radiation characteristics of the antenna 100 at three frequency points: 24 GHz, 28 GHz, and 32 GHz. Solid lines or solid-colored curves represent simulation results, while dotted or dashed lines represent measured data. Different colors correspond to different frequencies: 24 GHz corresponds to black or blue, 28 GHz to green or pink, and 32 GHz to orange or red. Compared to the vertical plane radiation pattern in the previous figure, the horizontal plane radiation pattern in this figure presents a more omnidirectional or weakly directional ring radiation characteristic. The main lobe level is relatively high and distributed near multiple angles such as 0 degrees, 90 degrees, 180 degrees, and 270 degrees. The sidelobes are dense, but their average voltage is below -20 dB, indicating that the horizontal omnidirectional transmission array antenna 100 has excellent omnidirectional radiation uniformity and low sidelobe characteristics in the azimuth plane. The high overlap between the measured and simulated curves with the same polarization verifies the accuracy of the modeling. The cross-polarization level generally remained below -25dB, with some areas reaching -30dB, indicating good polarization purity. Overall, the radiation patterns at the three frequencies were similar in shape with slight variations in amplitude, reflecting that the horizontal omnidirectional transmission array antenna 100 possesses a stable radiation mode and good repeatability in the K-band.

[0031] like Figures 1 to 3 As shown, in one embodiment, the number of layers in the transmission array layer 21 is five.

[0032] In this embodiment, the five-layer transmission array 21 can receive most of the energy in the quasi-spherical electromagnetic waves radiated from the feed 10, making it a suitable layer number scheme that balances receiving efficiency and structural volume of the horizontal omnidirectional transmission array antenna 100. When the number of transmission array layers 21 is less than five, the ability of the transmission array 20 to capture quasi-spherical electromagnetic waves weakens, resulting in low gain and insufficient sidelobe suppression capability of the horizontal omnidirectional transmission array antenna 100. When the number of transmission array layers 21 is more than five, the improvement in radiation performance of the horizontal omnidirectional transmission array antenna 100 tends to plateau, while the structural volume, transmission loss, and manufacturing cost increase accordingly. Therefore, setting the number of transmission array layers 21 to five helps to obtain relatively ideal gain and sidelobe level performance while maintaining the compact size of the horizontal omnidirectional transmission array antenna 100.

[0033] like Figure 7 As shown, in one embodiment, each transceiver unit 212 includes: The receiving dipole unit 2121 is positioned close to the feed source 10 and is used to receive quasi-spherical electromagnetic waves. The transmitting dipole unit 2122 is positioned away from the feed source 10 and is used to radiate uniform planar electromagnetic waves in the horizontal plane. The delay transmission line 2123 is located between the receiving dipole unit 2121 and the transmitting dipole unit 2122, and connects the receiving dipole unit 2121 and the transmitting dipole unit 2122. The delay transmission line 2123 is configured to adjust its physical length to adjust the phase difference between the quasi-spherical electromagnetic wave received by the corresponding receiving dipole unit 2121 and the horizontal uniform planar electromagnetic wave radiated by the transmitting dipole unit 2122, thereby changing the phase distribution between different transmission array layers 21 to transform the spherical phase distribution of the quasi-spherical electromagnetic wave into the planar equal phase distribution of the horizontal uniform planar electromagnetic wave.

[0034] In this embodiment, each transmission array layer 21 includes sixteen periodically arranged transceiver units 212. This number is beneficial for forming a uniform sampling interval in the azimuth plane, enabling the horizontal omnidirectional transmission array antenna 100 to obtain a continuous and stable phase modulation effect within a 360-degree range, avoiding grating lobes or radiation discontinuities caused by excessive spacing between the transceiver units 212. Each transceiver unit 212 consists of a receiving dipole unit 2121, a transmitting dipole unit 2122, and a delay transmission line 2123. The receiving dipole unit 2121 is located inside the corresponding annular substrate 211, and the transmitting dipole unit 2122 is located outside the corresponding annular substrate 211. This allows the receiving dipole unit 2121 to be closer to the feed source 10 for efficient capture of quasi-spherical electromagnetic waves, while the transmitting dipole unit 2122 radiates towards external space, which helps reduce transceiver coupling interference and optimize the outward radiation path of the uniform planar electromagnetic waves in the horizontal plane. The quasi-spherical electromagnetic wave radiated by the feed 10 is first received by the receiving dipole element 2121 and propagated along the delay transmission line 2123. Finally, it is re-radiated by the transmitting dipole element 2122 as a uniform horizontal plane electromagnetic wave. By adjusting the physical length of the delay transmission line 2123, the phase difference between the quasi-spherical electromagnetic wave received by the receiving dipole element 2121 and the uniform horizontal plane electromagnetic wave radiated by the transmitting dipole element 2122 can be changed. This adjusts the phase distribution between different transmission array layers 21, thereby transforming the spherical phase distribution at the receiving dipole element 2121 into a planar equiphase distribution at the transmitting dipole element 2122, achieving uniform radiation characteristics of the horizontal omnidirectional transmission array antenna 100 in the azimuth plane.

[0035] like Figure 7 As shown, in one embodiment, the delay transmission line 2123 includes a receiving section 21231, a transmitting section 21232, and a wire conductor 21233 connecting the receiving section 21231 and the transmitting section 21232. The receiving section 21231 is connected to the receiving dipole unit 2121, and the transmitting section 21232 is connected to the transmitting dipole unit 2122. The receiving section 21231 and the transmitting section 21232 are symmetrically arranged about the centerline of the wire conductor 21233. The wire conductor 21233 includes a first L-shaped segment connected to the receiving section 21231, a second L-shaped segment connected to the transmitting section 21232, and a U-shaped segment connecting the first L-shaped segment and the second L-shaped segment.

[0036] In this embodiment, the aforementioned bent structure of the delay transmission line 2123 allows for the extension of its physical length within the narrow cross-section of the transceiver unit 212 by utilizing a meandering path formed by the first L-shaped segment, the second L-shaped segment, and the U-shaped segment. This achieves the target phase difference without increasing the overall size of the transceiver unit 212. Figure 8As shown in the figure, this diagram illustrates the transmission characteristics of two different transceiver units 212 operating in the 23GHz to 33GHz frequency band. One transceiver unit 212 has a delay transmission line 2123 length l_delay of 1.3mm, while the other has a delay transmission line 2123 length l_delay of 0.5mm. Both amplitude curves are close to 0dB, and the insertion loss is approximately 0.5dB to 1dB, indicating that both have low-loss transmission performance. The phase response exhibits an approximately linear negative slope, and the phase change of the transceiver unit 212 with a delay transmission line 2123 length l_delay of 1.3mm is steeper, differing by approximately 200 degrees at 30GHz, corresponding to a larger group delay. This result verifies the design principle that by increasing the length l_delay of the delay transmission line 2123, which consists of receiving line segment 21231, transmitting line segment 21232, and line conductor 21233, the phase delay between receiving dipole unit 2121 and transmitting dipole unit 2122 can be effectively controlled. This allows the delay transmission line 2123 to accurately match the required phase compensation amount within a limited space, ensuring that the transmission array layer 21 accurately converts the quasi-spherical electromagnetic wave into a uniform horizontal plane electromagnetic wave.

[0037] like Figure 9 As shown, in one embodiment, the feed source 10 includes: The monopole radiator 11 is arranged along the axis of the horizontal omnidirectional transmission array antenna 100; The feeding structure 12 has an odd number of layers in the transmission array layer 21. The feeding structure 12 is located in the middle layer of the transmission array layer 21. The output end of the feeding structure 12 is connected to the input end of the monopole radiator 11 to provide radio frequency excitation signals to the monopole radiator 11 to excite the monopole radiator 11 to generate quasi-spherical electromagnetic waves.

[0038] In this embodiment, the monopole radiator 11 extends along the axial direction of the horizontal omnidirectional transmission array antenna 100, and the feeding structure 12 is connected to the input terminal of the monopole radiator 11 to transmit radio frequency excitation signals to the monopole radiator 11, so that the monopole radiator 11 forms a rotationally symmetric current distribution in the azimuth plane and generates quasi-spherical electromagnetic waves.

[0039] From the perspectives of symmetrical phase distribution, uniform energy distribution, and adaptation to the symmetrical beam-constrained reflector 30, placing the feed structure 12 in the middle transmission array layer 21 helps maintain the axial path symmetry and phase symmetry of the quasi-spherical electromagnetic wave, promoting uniform energy distribution among the transmission array layers 21. If the feed structure 12 deviates from the middle transmission array layer 21, the distance the quasi-spherical electromagnetic wave reaches the upper and lower transmission array layers 21 will be inconsistent, leading to uneven energy distribution and phase deviation between layers. Such energy unevenness caused by spatial asymmetry cannot be compensated for simply by adjusting the physical length of each layer of delay transmission line 2123. Therefore, placing the feed structure 12 in the middle transmission array layer 21 and using an odd number of transmission array layers 21 helps to achieve balanced energy distribution and symmetrical phase control among the transmission array layers 21 of the horizontal omnidirectional transmission array antenna 100, improving the consistency of overall radiation performance.

[0040] like Figure 9 As shown, in one embodiment, the power supply structure 12 includes: The power supply network 121 is located on one side of the annular substrate 211 and is used to receive the fed radio frequency excitation signal, divide the radio frequency excitation signal into multiple equal amplitude and in-phase signals and output them after impedance matching. The number of equal amplitude and in-phase signals is even. The radiating structure 122 is disposed on the side of the annular substrate 211 away from the feed network 121. The input end of the radiating structure 122 is connected to the output end of the feed network 121, and the output end of the radiating structure 122 is connected to the input end of the monopole radiator 11. It is used to receive the impedance-matched equal-amplitude and in-phase signal and radiate it to the monopole radiator 11.

[0041] In this embodiment, the feed network 121 and the radiating structure 122 are respectively arranged on both sides of the annular substrate 211, which helps to reduce electromagnetic coupling interference between the feed network 121 and the radiating structure 122, and at the same time facilitates a compact layout and electrical interconnection of the feed network 121 and the radiating structure 122 within a limited space. The feed network 121 divides the radio frequency excitation signal into an even number of equal-amplitude and in-phase signals, which helps to form a symmetrical signal distribution path on the annular substrate 211. This allows each equal-amplitude and in-phase signal to be converged by the radiating structure 122 and uniformly excite the monopole radiator 11, thereby maintaining the rotational symmetry characteristics of the quasi-spherical electromagnetic wave in the azimuth plane. The radiating structure 122 receives the impedance-matched equal-amplitude and in-phase signals and radiates them to the monopole radiator 11. Impedance matching reduces the reflection loss of the radio frequency excitation signal during transmission and improves the feeding efficiency. The equal-amplitude and in-phase characteristics help the monopole radiator 11 generate quasi-spherical electromagnetic waves with consistent phase, further improving the radiation circularity and gain stability of the horizontal omnidirectional transmission array antenna 100.

[0042] like Figure 9As shown, in one embodiment, the power supply network 121 includes: A microstrip power divider has multiple signal output terminals. The microstrip power divider is used to divide the radio frequency excitation signal into multiple equal amplitude and in-phase signals, and convert the multiple equal amplitude and in-phase signals into multiple balanced signals. The signal output terminal is used to output a balanced signal. The radiating structure 122 includes multiple bent dipoles 1221; Multiple bent dipoles 1221 are arranged at equal intervals along the circumference; The number of bent dipoles 1221 is even, and multiple bent dipoles 1221 are connected to multiple signal output terminals in a one-to-one correspondence. The bent dipole 1221 is used to receive the balance signal and radiate the received balance signal to the monopole radiator 11.

[0043] In this embodiment, the microstrip power divider includes a power divider body, multiple microstrip lines, and a coupling structure. The RF excitation signal, after being input via a central metal probe, is split into multiple equal-amplitude, in-phase signals by the power divider body. These signals are then output one-to-one from the power divider body's multiple output terminals to the multiple microstrip lines, transmitted via the microstrip lines to the coupling structure, and after impedance matching by the coupling structure, coupled to the radiation structure 122 through its multiple signal output terminals. The coupling structure converts the unbalanced equal-amplitude, in-phase signals into balanced signals, adapting the balanced signals to the balanced feed requirements of the bent dipole 1221, thereby delivering a balanced signal with consistent phase and impedance matching to the radiation structure 122. The bent shape of the two arms of the bent dipole 1221 is used to broaden the radiation pattern of the feed 10 in the azimuth plane. Since the horizontal omnidirectional transmission array antenna 100 requires the feed 10 to have uniform omnidirectional radiation capability in the horizontal plane, and the azimuth radiation coverage and roundness performance of the straight dipole are insufficient, bending the two arms of the bent dipole 1221 can effectively widen the azimuth radiation beam, making the radiation of the feed 10 more uniform in the entire azimuth angle. Thus, when multiple bent dipoles 1221 receive balanced signals and radiate them to the monopole radiator 11, a more ideal quasi-spherical electromagnetic wave excitation field can be formed.

[0044] like Figure 9 As shown, in one embodiment, the microstrip power divider is a 1-to-4 microstrip power divider; There are four microstrip lines, and adjacent microstrip lines are set orthogonally. There are four coupling input terminals and four coupling output terminals respectively; There are four bent dipoles 1221, and two adjacent bent dipoles 1221 are orthogonally arranged.

[0045] In this embodiment, the radiating structure 122 employs four bent dipoles 1221, presenting an overall four-way orthogonal layout, which is a simple and stable centrally symmetrical structure. The four signal outputs of the 1-to-4 microstrip power divider are connected one-to-one with the inputs of the four microstrip lines, allowing the four equal-amplitude, in-phase signals to be transmitted independently via the four microstrip lines. The outputs of the four microstrip lines are connected one-to-one with the four coupling inputs of the coupling structure, allowing the equal-amplitude, in-phase signals to be converted into balanced signals by the coupling structure and then fed into the four bent dipoles 1221 through the four coupling outputs, thus promoting a uniform radiation field distribution of the four bent dipoles 1221 in the azimuth plane. If a 1-to-6 microstrip power divider is used and the number of bent dipoles 1221 is increased to six, the bent dipoles 1221 are arranged more densely, which easily enhances the mutual coupling effect between the bent dipoles 1221, resulting in a deterioration in the omnidirectional pattern circularity of the horizontal omnidirectional transmission array antenna 100. Therefore, using a one-to-four microstrip power divider with four orthogonally arranged bent dipoles 1221 is beneficial to achieving good omnidirectional radiation consistency while maintaining a compact structure.

[0046] like Figure 9 As shown, in one embodiment, the power supply structure 12 further includes: Multiple matching parasitic units 123 are disposed on the side of the annular substrate 211 away from the feed network 121 and located on the periphery of the radiating structure 122. The positions of the multiple matching parasitic units 123 correspond one-to-one with the positions of the multiple bent dipoles 1221. The matching parasitic unit 123 is used to adjust the input impedance of the bent dipole 1221 to adjust the impedance matching between the feed source 10 and the feed network 121, and to smooth the radiation pattern of the bent dipole 1221 to compensate for the radiation circularity of the horizontal omnidirectional transmission array antenna 100 in the azimuth plane.

[0047] In this embodiment, multiple matching parasitic units 123 are arranged around the radiating structure 122, and the positions of the multiple matching parasitic units 123 correspond one-to-one with the positions of multiple bent dipoles 1221. By utilizing the adjustment effect of the matching parasitic units 123 on the input impedance of the corresponding bent dipoles 1221, the impedance matching state between the feed source 10 and the feed network 121 is improved. At the same time, by utilizing the smoothing effect of the matching parasitic units 123 on the radiation pattern of the bent dipoles 1221, the radiation circularity deviation of the horizontal omnidirectional transmission array antenna 100 in the azimuth plane is compensated, thereby improving the impedance matching performance and azimuth radiation circularity of the horizontal omnidirectional transmission array antenna 100.

[0048] like Figure 10As shown, in one embodiment, the transceiver units 212 of at least two transmission array layers 21 are staggered along the axial direction of the horizontal omnidirectional transmission array antenna 100 to form a plurality of first subarray groups 21201 and a plurality of second subarray groups 21202 along the axial direction of the horizontal omnidirectional transmission array antenna 100. The plurality of first subarray groups 21201 and the plurality of second subarray groups 21202 are alternately arranged circumferentially to compensate for the azimuth pattern non-circularity of the horizontal omnidirectional transmission array antenna 100 caused by the periodic arrangement of the transceiver units 212.

[0049] In this embodiment, each transmission array layer 21 employs sixteen transceiver units 212 evenly arranged, enabling the azimuth pattern non-circularity of the horizontal omnidirectional transmission array antenna 100 to be controlled within 10 dB in the 32 GHz band. Based on this, this embodiment divides the transceiver units 212 of at least two transmission array layers 21 into multiple first subarray groups 21201 and multiple second subarray groups 21202, and arranges the multiple first subarray groups 21201 and multiple second subarray groups 21202 alternately along the circumferential direction. Since the periodic arrangement of the transceiver unit 212 is prone to causing periodic fluctuations in radiation intensity in the azimuth plane, and after the multiple first subarray groups 21201 and multiple second subarray groups 21202 are arranged alternately in the circumferential direction, the phase and amplitude distribution of the radiation field of adjacent first subarray groups 21201 and second subarray groups 21202 in the azimuth plane are different. This causes the radiation lobes and nulls originally generated by the periodic arrangement to be spatially misaligned and superimposed, thereby weakening the periodic fluctuations in the azimuth plane radiation intensity. This effectively compensates for the non-circularity of the azimuth plane radiation pattern caused by the periodic arrangement of the transceiver unit 212 in the horizontal omnidirectional transmission array antenna 100, and further improves the azimuth plane radiation circularity of the horizontal omnidirectional transmission array antenna 100. Meanwhile, the transceiver units 212 of at least two transmission array layers 21 are staggered along the axial direction of the horizontal omnidirectional transmission array antenna 100, so that multiple first subarray groups 21201 and multiple second subarray groups 21202 are also staggered in the axial direction. The synergistic effect of the multiple first subarray groups 21201 and multiple second subarray groups 21202 being alternately arranged in the circumferential direction makes the radiation field distribution of the horizontal omnidirectional transmission array antenna 100 in three-dimensional space more uniform, avoiding the limiting effect of subarray arrangement in a single plane on radiation circularity, thereby enabling the horizontal omnidirectional transmission array antenna 100 to maintain stable azimuth radiation circularity performance in a wider frequency band.

[0050] like Figure 10 As shown, in one embodiment, a reference plane is defined that is perpendicular to the horizontal plane of the transceiver unit 212 of the transceiver array layer 21 along the central axis of the horizontal omnidirectional transceiver array antenna 100. The projections of the transceiver units 212 of the adjacent first subarray group 21201 and the transceiver units 212 of the second subarray group 21202 onto the reference plane have a preset rotation angle.

[0051] In this embodiment, the preset rotation angle is set to 11.25°. The selection of this value is directly related to the structural feature that each transmission array layer 21 uses sixteen transceiver units 212 arranged uniformly. Since the sixteen transceiver units 212 are evenly distributed around the circumference of the horizontal omnidirectional transmission array antenna 100, and the circumferential angle between two adjacent transceiver units 212 is 22.5°, setting the preset rotation angle to half of this circumferential angle, i.e., 11.25°, allows the projections of the transceiver units 212 of the first subarray group 21201 and the transceiver units 212 of the second subarray group 21202 onto the reference plane to be exactly offset by half the distance between transceiver units 212. This results in the peak and valley values ​​of the radiation field of the first subarray group 21201 and the second subarray group 21202 on the azimuth plane being interleaved and superimposed, effectively smoothing the azimuth plane radiation pattern fluctuations caused by the periodic arrangement of the transceiver units 212. This, in turn, compensates for the radiation circularity deviation of the horizontal omnidirectional transmission array antenna 100 on the azimuth plane, enabling the horizontal omnidirectional transmission array antenna 100 to maintain relatively uniform azimuth plane radiation characteristics in the 32GHz frequency band.

[0052] like Figures 1 to 3 As shown, in one embodiment, at least one beam-constrained reflector 30 has a reflective surface 31 on the side facing the transmission array 20, and the reflective surface 31 is a conical surface.

[0053] In this embodiment, the conical surface is mainly used to guide the quasi-spherical electromagnetic waves radiated by the feed 10 into the transmission array 20. By setting the conical surface, the quasi-spherical electromagnetic waves that overflow along the axial direction can also be obliquely reflected to the transmission array 20, so that the quasi-spherical electromagnetic waves that did not directly illuminate the transmission array 20 are redirected and participate in the radiation process of the transmission array 20, thereby improving the utilization efficiency of the quasi-spherical electromagnetic waves and improving the radiation performance of the horizontal omnidirectional transmission array antenna 100. At the same time, the conical surface is a centrally symmetric structure, which is highly matched with the geometry of the circular transmission array 20 and the feed 10. This makes the reflection path of the quasi-spherical electromagnetic waves on the conical surface uniformly distributed in the circumferential direction, avoiding additional azimuth radiation asymmetry caused by the mismatch between the shape of the reflecting surface 31 and the geometry of the transmission array 20 or the feed 10, which is beneficial to maintaining the radiation circularity of the horizontal omnidirectional transmission array antenna 100 in the azimuth plane.

[0054] The present invention also proposes a wireless communication system, which includes a horizontal omnidirectional transmission array antenna 100. The specific structure of the horizontal omnidirectional transmission array antenna 100 is as described in the above embodiments. Since the present wireless communication system adopts all the technical solutions of all the above embodiments, it has at least all the beneficial effects brought about by the technical solutions of the above embodiments, which will not be described in detail here.

[0055] The above description is merely an exemplary embodiment of the present invention and does not limit the patent scope of the present invention. Any equivalent structural transformations made using the contents of the present invention specification and drawings under the technical concept of the present invention, or direct / indirect applications in other related technical fields, are included within the patent protection scope of the present invention.

Claims

1. A horizontal omnidirectional transmission array antenna, characterized in that, include: The feed source, arranged along the axis of the horizontal omnidirectional transmission array antenna, is used to receive the input radio frequency excitation signal and generate quasi-spherical electromagnetic waves. A transmission array is coaxially arranged around the feed source. The transmission array includes at least two transmission array layers stacked along the axial direction of the horizontal omnidirectional transmission array antenna. Each transmission array layer includes a circular substrate and a plurality of transceiver units distributed in a circular array on the circular substrate. The transceiver units are used to receive the quasi-spherical electromagnetic wave and perform phase compensation on the quasi-spherical electromagnetic wave to convert the quasi-spherical electromagnetic wave into a horizontal uniform planar electromagnetic wave before radiation. Two beam-constrained reflectors are arranged on opposite sides of the horizontal omnidirectional transmission array antenna along the axis of the antenna. The two beam-constrained reflectors are connected through the transmission array. A feed source is provided between the two beam-constrained reflectors to collect quasi-spherical electromagnetic waves radiated by the feed source toward the beam-constrained reflectors and guide the collected quasi-spherical electromagnetic waves to the transmission array.

2. The horizontal omnidirectional transmission array antenna as described in claim 1, characterized in that, Each of the transceiver units includes: A receiving dipole unit is positioned close to the feed source to receive the quasi-spherical electromagnetic waves; A transmitting dipole unit is positioned away from the feed source to radiate uniform planar electromagnetic waves on the horizontal plane. A delay transmission line is located between the receiving dipole unit and the transmitting dipole unit, and connects the receiving dipole unit and the transmitting dipole unit. The delay transmission line is configured to adjust its physical length to adjust the phase difference between the quasi-spherical electromagnetic wave received by the corresponding receiving dipole unit and the horizontal uniform planar electromagnetic wave radiated by the transmitting dipole unit, thereby changing the phase distribution between different transmission array layers to transform the spherical phase distribution of the quasi-spherical electromagnetic wave into the planar equal phase distribution of the horizontal uniform planar electromagnetic wave.

3. The horizontal omnidirectional transmission array antenna as described in claim 1, characterized in that, The feed source includes: A monopole radiator is arranged along the axial direction of the horizontal omnidirectional transmission array antenna; The feeding structure has an odd number of transmission array layers. The feeding structure is located in the middle transmission array layer. The output end of the feeding structure is connected to the input end of the monopole radiator to provide a radio frequency excitation signal to the monopole radiator to excite the monopole radiator to generate the quasi-spherical electromagnetic wave.

4. The horizontal omnidirectional transmission array antenna as described in claim 3, characterized in that, The power supply structure includes: A power supply network is provided on one side of the annular substrate to receive the fed radio frequency excitation signal, divide the radio frequency excitation signal into multiple equal-amplitude and in-phase signals and output them after impedance matching, wherein the number of equal-amplitude and in-phase signals is even. A radiating structure is disposed on the side of the annular substrate away from the feed network. The input end of the radiating structure is connected to the output end of the feed network, and the output end of the radiating structure is connected to the input end of the monopole radiator. It is used to receive the impedance-matched equal-amplitude and in-phase signal and radiate it to the monopole radiator.

5. The horizontal omnidirectional transmission array antenna as described in claim 4, characterized in that, The power supply network includes: A microstrip power divider has multiple signal output terminals. The microstrip power divider is used to divide the radio frequency excitation signal into multiple equal-amplitude and in-phase signals, and convert the multiple equal-amplitude and in-phase signals into multiple balanced signals. The signal output terminals are used to output a balanced signal. The radiating structure includes multiple bent dipoles; The multiple bent dipoles are arranged at equal intervals along the circumferential direction; The number of the bent dipoles is even, and the multiple bent dipoles are connected one-to-one with the multiple signal output terminals; The bent dipole is used to receive the balance signal and radiate the received balance signal to the monopole radiator.

6. The horizontal omnidirectional transmission array antenna as described in claim 5, characterized in that, The power supply structure also includes: Multiple matching parasitic units are disposed on the side of the annular substrate away from the feed network and located on the periphery of the radiating structure. The positions of the multiple matching parasitic units correspond one-to-one with the positions of the multiple bent dipoles. The matching parasitic unit is used to adjust the input impedance of the bent dipole to adjust the impedance matching between the feed source and the feed network, and to smooth the radiation pattern of the bent dipole to compensate for the radiation circularity of the horizontal omnidirectional transmission array antenna in the azimuth plane.

7. The horizontal omnidirectional transmission array antenna as described in claim 1, characterized in that, At least two transceiver units of the transmission array layer are staggered along the axial direction of the horizontal omnidirectional transmission array antenna to form a plurality of first subarray groups and a plurality of second subarray groups along the axial direction of the horizontal omnidirectional transmission array antenna. The plurality of first subarray groups and the plurality of second subarray groups are alternately arranged circumferentially to compensate for the non-circularity of the azimuth pattern of the horizontal omnidirectional transmission array antenna caused by the periodic arrangement of the transceiver units.

8. The horizontal omnidirectional transmission array antenna as described in claim 7, characterized in that, A reference plane is defined that is perpendicular to the horizontal plane along the central axis of the horizontal omnidirectional transmission array antenna and is the transceiver unit of the transmission array layer. The projections of the transceiver units of the first subarray group and the transceiver units of the second subarray group onto the reference plane have a preset rotation angle.

9. The horizontal omnidirectional transmission array antenna as described in claim 1, characterized in that, At least one of the beam-constrained reflectors has a reflective surface on the side facing the transmission array, and the reflective surface is a conical surface.

10. A wireless communication system, characterized in that, Includes a horizontal omnidirectional transmission array antenna as described in any one of claims 1 to 9.

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