Method and device for optimizing output ripple of charging module, controller and charging equipment

Abstract

The application provides an output ripple optimization method and device of a charging module, a controller and a charging equipment. The method comprises the following steps: obtaining an output current actual value and an output current given value of the charging module; performing correlation processing on the output current actual value and the output current given value based on the same amplification factor to obtain a gain current difference value, and calculating a current compensation value according to the gain current difference value; superimposing the current compensation value and a current loop output value of the charging module to obtain a compensated current loop output value, and controlling the charging module based on the compensated current loop output value. The above method can solve the problem that the compensation is invalid due to the weak error signal after traditional sampling, form a cooperative mechanism of basic current control and ripple special compensation, make up for the defect of insufficient low-frequency gain of the traditional single current loop, quickly respond to the output current fluctuation caused by the bus voltage ripple, and actively cancel the low-frequency ripple.

Description

Technical Field

[0001] This invention relates to the field of charging module control technology, and in particular to a method, apparatus, controller and charging equipment for optimizing the output ripple of a charging module. Background Technology

[0002] In power electronic systems, the charging module includes a converter and a PFC (Power Factor Correction) circuit. This structure constitutes the core collaborative architecture for power conversion and grid connection, and is widely used in new energy power generation, industrial drives, uninterruptible power supplies, energy storage systems, and new energy vehicle charging. The PFC circuit improves the waveform of the input current on the grid side, increases the power factor, reduces harmonic pollution, and provides stable DC bus power to the downstream converter. The converter receives the output of the PFC circuit, realizing the efficient conversion of DC power into constant voltage / constant current charging power adapted to the battery. The collaborative performance of the two directly determines the power utilization efficiency, grid compatibility, and output power quality of the entire power electronic system. Among them, the stability of the converter's output current depends not only on the front-end optimization of the PFC, but also on the ripple suppression capability of its own control strategy.

[0003] However, DC bus voltage ripple is susceptible to influences from power frequency rectification and switching action of switching transistors, resulting in a fixed-frequency bus voltage ripple. This ripple is directly transmitted to the output of the charging module through the coupling effect of the resonant cavity, DC / DC power conversion topology, or power loop, causing synchronous low-frequency ripple in the output current. Furthermore, the battery packs and capacitive filter loads commonly found at the charging module output are sensitive to current changes, further amplifying the impact of ripple on output characteristics. This leads to excessive ripple peak values, severely affecting battery life, charging consistency, normal BMS operation, and the normal operation of downstream equipment. Summary of the Invention

[0004] This invention provides a method, apparatus, controller, and charging device for optimizing the output ripple of a charging module, in order to solve the problem of large output current ripple in charging modules.

[0005] In a first aspect, embodiments of the present invention provide a method for optimizing the output ripple of a charging module, comprising: Obtain the actual value and the setpoint value of the output current of the charging module; The actual value of the output current and the given value of the output current are correlated based on the same amplification factor to obtain the gain current difference, and the current compensation value is calculated based on the gain current difference. The current compensation value is superimposed on the current loop output value of the charging module to obtain the compensated current loop output value, and the charging module is controlled based on the compensated current loop output value.

[0006] In one possible implementation, the correlation processing between the actual value of the output current and the given value of the output current based on the same amplification factor includes: Both the actual value of the output current and the given value of the output current are amplified by a preset factor; The gain current difference is obtained by subtracting the actual value of the output current from the amplified given value of the output current.

[0007] In one possible implementation, calculating the current compensation value based on the gain current difference includes: The gain current difference is input into the first PI controller to obtain the current compensation value.

[0008] In one possible implementation, after calculating the current compensation value based on the gain current difference, the method further includes: The current compensation value is limited using a first preset range; Accordingly, the step of superimposing the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value includes: The current compensation value after the limiting process is superimposed on the current loop output value of the charging module to obtain the compensated current loop output value.

[0009] In one possible implementation, the correlation processing between the actual value of the output current and the given value of the output current based on the same amplification factor includes: If the difference between the actual output current value and the given output current value is less than a preset difference threshold, then the actual output current value and the given output current value are correlated based on the same amplification factor.

[0010] In one possible implementation, before superimposing the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value, the method further includes: The output current difference is obtained by subtracting the actual output current value from the given output current value. The output current difference is input into the second PI controller to obtain the current loop output value.

[0011] In one possible implementation, controlling the charging module based on the compensated current loop output value includes: Obtain the voltage loop output value of the charging module; The larger of the compensated current loop output value and the voltage loop output value is selected as the target control variable; The target control quantity is used to generate a PWM signal to control the charging module.

[0012] Secondly, embodiments of the present invention provide an output ripple optimization device for a charging module, comprising: The data acquisition module is used to acquire the actual value and the setpoint value of the output current of the charging module; The current compensation value calculation module is used to correlate the actual value of the output current and the given value of the output current based on the same amplification factor to obtain the gain current difference, and calculate the current compensation value based on the gain current difference. The control module is used to superimpose the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value, and control the charging module based on the compensated current loop output value.

[0013] Thirdly, embodiments of the present invention provide a controller, including a memory, a processor, and a computer program stored in the memory and executable on the processor, wherein the processor executes the computer program to implement the steps of the method as described in the first aspect or any possible implementation of the first aspect.

[0014] Fourthly, embodiments of the present invention provide a charging device, which includes the controller described in the third aspect above.

[0015] This invention provides a method, apparatus, controller, and charging device for optimizing the output ripple of a charging module. The method first correlates the actual output current value and the given output current value based on the same amplification factor to obtain the gain current difference. This overcomes the limitations of traditional solutions that directly compensate for minute ripple errors, amplifying and extracting ripple errors that were originally masked by noise, providing clear and reliable feedback for subsequent compensation. This solves the problem of compensation failure caused by weak error signals after traditional sampling. Secondly, by calculating the current compensation value and superimposing it onto the original current loop output, a synergistic mechanism of basic current control and ripple-specific compensation is formed. This compensates for the insufficient low-frequency gain of traditional single current loops, enabling rapid response to output current fluctuations caused by bus voltage ripple, achieving active cancellation of low-frequency ripple, and significantly improving the operational stability of downstream capacitive loads. Attached Figure Description

[0016] To more clearly illustrate the technical solutions in the embodiments of the present invention, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0017] Figure 1This is an application scenario diagram of the output ripple optimization method for the charging module provided in this embodiment of the invention; Figure 2 This is a flowchart illustrating the implementation of the output ripple optimization method for the charging module provided in this embodiment of the invention. Figure 3 This is a schematic diagram of the output current before and after the sampling bandwidth change provided in an embodiment of the present invention; Figure 4 This is a control block diagram of the output ripple optimization method for the charging module provided in this embodiment of the invention; Figure 5 This is a schematic diagram of the output ripple optimization device for the charging module provided in an embodiment of the present invention; Figure 6 This is a schematic diagram of the controller provided in an embodiment of the present invention. Detailed Implementation

[0018] In the following description, specific details such as particular system architectures and techniques are set forth for illustrative purposes and not for limitation, in order to provide a thorough understanding of the embodiments of the invention. However, those skilled in the art will understand that the invention can be implemented in other embodiments without these specific details. In other instances, detailed descriptions of well-known systems, apparatuses, circuits, and methods are omitted so as not to obscure the description of the invention with unnecessary detail.

[0019] To make the objectives, technical solutions, and advantages of the present invention clearer, specific embodiments will be described below in conjunction with the accompanying drawings.

[0020] Figure 1 This diagram illustrates an application scenario of the output ripple optimization method for a charging module provided in this embodiment of the invention. Figure 1As shown, the charging module includes a DC / DC converter and a PFC circuit. The input of the DC / DC converter is connected to the output of the PFC circuit, and the input of the PFC circuit is connected to the power grid. The PFC circuit is used to improve the waveform of the input current on the grid side, increase the power factor, and suppress harmonic pollution, ensuring that the system meets the grid connection requirements. It also provides stable high-voltage DC bus power to the downstream DC / DC converter. The DC / DC converter receives the output of the PFC circuit, achieving efficient isolation and voltage regulation of DC power into constant-voltage, constant-current, and constant-power charging power adapted to power batteries and energy storage batteries. The synergistic performance of these two components directly determines the energy utilization efficiency, grid compatibility, and output power quality of the entire power electronic system. The stability of the charging module's output current depends not only on the front-end ripple suppression of the PFC but also on the precise cancellation capability of the DC / DC converter control strategy for residual ripple. Therefore, optimizing the control technology of the charging synergistic architecture based on the PFC-DC / DC converter, especially the smooth control of the charging module's output current, has become a core research direction for improving the overall performance of new energy charging and energy storage systems.

[0021] However, the presence of output current ripple in charging modules has always been a key issue restricting their power quality and charging reliability. This ripple arises from several causes: First, the DC bus voltage of the charging module is susceptible to power frequency rectification, PFC switching, and grid fluctuations, generating a fixed-frequency (e.g., 100Hz) bus voltage ripple. This ripple is directly transmitted to the output terminal through the coupling effect of the resonant cavity, DC / DC power conversion topology, or power loop, resulting in synchronous low-frequency ripple in the output current. Second, traditional current sampling circuits have design limitations, such as overly conservative filter parameters and insufficient sampling bandwidth, making it impossible to accurately capture the true low-frequency ripple components in the output current, thus lacking reliable feedback for subsequent control strategies. Furthermore, the battery pack and its associated capacitive filter load connected to the charging module output terminal are highly sensitive to current ripple, further amplifying its impact on output characteristics and causing ripple peak values ​​to exceed limits. This not only accelerates battery aging, reduces battery cycle life, and affects the charging consistency of multi-cell batteries, but may also trigger misjudgments in the battery management system, and in severe cases, even affect charging safety and the normal operation of downstream equipment.

[0022] To address the aforementioned issues, this embodiment provides a method for optimizing the output ripple of a charging module. (See [link to relevant documentation]). Figure 2 The flowchart illustrating the implementation of the output ripple optimization method for the charging module provided in this embodiment of the invention is described in detail below: S101: Obtain the actual value of the output current and the setpoint value of the output current of the charging module.

[0023] The output ripple optimization method for the charging module provided in this embodiment is specifically applied to the controller of the DC / DC converter in the charging module. A current sampling circuit is installed at the output terminal of the charging module to detect the actual value of the output current of the DC / DC converter in the charging module. The output current setpoint is the current value that the controller expects the charging module to output.

[0024] Specifically, the existing current sampling circuit has a small sampling bandwidth, which cannot reflect the true ripple situation for ripple control, and subsequent software strategies cannot be accurately implemented. Based on the analysis of the original ripple waveform, it can be seen that the high ripple is mainly caused by the low-frequency ripple peaks around 50Hz.

[0025] In order to more accurately sample the output current ripple, this embodiment needs to modify the parameters of the current sampling circuit to improve the sampling bandwidth.

[0026] For example, by modifying the parameters of the current sampling circuit, the sampling bandwidth of the current sampling circuit can be increased to 3~4KHz. Preferably, the sampling bandwidth is 3.6KHz. After changing the sampling bandwidth of the current sampling circuit, the sampling ripple is more realistic and clear. Figure 3 , Figure 3 The diagram shows the output current before and after the sampling bandwidth change provided in this embodiment.

[0027] S102: Based on the same amplification factor, the actual value of the output current and the given value of the output current are correlated to obtain the gain current difference, and the current compensation value is calculated based on the gain current difference.

[0028] In this embodiment, the controller can subtract the actual output current value from the given output current value to obtain the output current difference. Then, it amplifies the output current difference by a preset factor to obtain the gain current difference. The preset factor needs to balance ripple prominence and noise suppression. If it is too small, the ripple error will still be masked by noise; if it is too large, the sampling noise will be amplified synchronously. The inherent noise of the current sampling circuit may cause loop oscillation. Therefore, the value range of the preset factor is 10~30.

[0029] Specifically, the output current difference is amplified by a preset factor to highlight minute ripple errors and improve the accuracy of subsequent ripple compensation.

[0030] The current compensation value is a signal used to cancel ripple, calculated based on the gain current difference, and must be out of phase with the original ripple.

[0031] S103: The current compensation value is superimposed with the current loop output value of the charging module to obtain the compensated current loop output value, and the charging module is controlled based on the compensated current loop output value.

[0032] In this embodiment, the current loop output value is the control output signal of the original current loop of the DC / DC converter in the charging module, which is responsible for basic current tracking. The current compensation value is added to the current loop output value of the DC / DC converter to obtain the compensated current loop output value. The compensated current loop output value can take into account both basic tracking and ripple suppression.

[0033] As can be seen from the above embodiments, this embodiment first correlates the actual value of the output current and the given value of the output current based on the same amplification factor to obtain the gain current difference. This breaks through the limitation of the traditional scheme that directly compensates for small ripple errors. It amplifies and extracts the ripple error that was originally masked by noise, providing a clear and reliable feedback basis for subsequent compensation and solving the problem that the weak error signal after traditional sampling leads to compensation failure. Secondly, by calculating the current compensation value and superimposing it on the original current loop output, a synergistic mechanism of basic current control and ripple-specific compensation is formed. This compensates for the deficiency of low-frequency gain in the traditional single current loop, enabling rapid response to output current fluctuations caused by bus voltage ripple, achieving active cancellation of low-frequency ripple, and significantly improving the operational stability of downstream capacitive loads.

[0034] In one possible implementation, refer to Figure 4 The specific implementation process of associating the actual value of the output current and the given value of the output current based on the same amplification factor in S102 includes: For the actual value of the output current I o_fdb and the output current setpoint I o_ref All magnified by the preset factor A; The amplified output current setpoint I o_ref Subtract the actual value of the output current I o_fdb The gain current difference is obtained.

[0035] In this embodiment, the output current setpoint I is... o_ref The amplification retains the target characteristics of a given value while amplifying the deviation dimension related to ripple. The actual output current I of the DC / DC converter is then amplified. o_fdb Amplification can amplify the ripple component in the actual output current, making it stand out from the noise.

[0036] The preset magnification factor can be determined based on the ripple amplitude, and the ripple amplitude is negatively correlated with the preset magnification factor. That is, the larger the ripple amplitude, the smaller the preset magnification factor, and the smaller the ripple amplitude, the larger the preset magnification factor.

[0037] Specifically, after obtaining the actual value I of the output current of the DC / DC converter... o_fdb Then, extract the actual value of the output current I. o_fdb The DC component in the output current is then used to determine the actual value of the output current I.o_fdb Subtract the DC component to obtain the ripple amplitude, and then determine the preset multiple based on the ripple amplitude.

[0038] To improve computational efficiency, this embodiment can extract the ripple amplitude of each sampling point for the output current signal of one sampling period, and then take the maximum value of the ripple amplitude of that sampling period to determine the preset multiple of that sampling period.

[0039] Assuming a preset multiplier of 20, both the output current setpoint and the actual output current value can be amplified by 20 times using a hardware operational amplifier to improve calculation speed and avoid software calculation errors. Alternatively, both the actual and setpoint output current values ​​can be amplified by the preset multiplier within the controller to improve the algorithm's adaptability.

[0040] After amplification, the given output current value after amplification by 20 times is subtracted from the actual output current value after amplification by 20 times to obtain the gain current difference. Then, the gain current difference is subjected to low-pass filtering to remove high-frequency noise after amplification. Finally, the gain current difference after high-frequency noise is filtered into the compensation algorithm to obtain the current compensation value.

[0041] As can be seen from the above embodiments, this embodiment first amplifies both the actual value and the given value of the output current by a preset factor. Then, the gain current difference is obtained by subtracting the actual value of the output current from the amplified given value. This allows the effective signal related to ripple to be amplified before error calculation. Since the given value and the actual value of the output current use the same amplification factor, the systematic noise introduced during the amplification process will cancel each other out in the subsequent subtraction operation, thereby preserving the true characteristics of the ripple error to the greatest extent and avoiding the offset of the compensation signal caused by noise interference. At the same time, the calculation logic of the difference between the given value and the actual value of the output current ensures that the sign of the gain current difference is strictly opposite to the direction of ripple deviation. This allows the current ripple to be offset by the current compensation value, improving the accuracy of ripple current elimination and making subsequent compensation more accurate and the loop more stable. It is especially suitable for ripple suppression scenarios with fixed frequency and small amplitude, such as low-frequency bus ripple, solving the problem of difficulty in separating noise and effective signal in traditional error calculation, and further improving the reliability and consistency of ripple suppression.

[0042] In one possible implementation, the specific implementation process of calculating the current compensation value based on the gain current difference in S102 includes: The gain current difference is input into the first PI controller to obtain the current compensation value. f comp .

[0043] In this embodiment, the calculation formula for the first PI controller is: .in, Indicates the current compensation value. Indicates the proportional parameter. Indicates the integration parameter. This represents the gain current difference.

[0044] As can be seen from the above embodiments, this embodiment inputs the gain current difference into the first PI controller to obtain the current compensation value. The first PI controller, as a mature and efficient linear control module, can respond instantly to the gain current difference with its proportional term, quickly generating the compensation component corresponding to the ripple error, ensuring that the compensation signal can keep up with the changing rhythm of low-frequency ripple, and making up for the problem of insufficient dynamic response of traditional loops. The integral term can accumulate small ripple steady-state error, gradually eliminating residual ripple caused by circuit parameter drift, sampling deviation, etc., to achieve deep ripple suppression, avoiding the limitation of traditional proportional control that can only attenuate ripple but cannot eliminate steady-state error.

[0045] In one possible implementation, after S102, the method provided in this embodiment further includes: The current compensation value is limited using a first preset range; Accordingly, the step of superimposing the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value includes: The current compensation value after the limiting process is superimposed on the current loop output value of the charging module to obtain the compensated current loop output value.

[0046] In this embodiment, the first preset range is a pre-set compensation value safety boundary, which can be determined based on the maximum output capacity of the charging module and the withstand current of the power devices. The lower limit of the first preset range is... f MIN The upper limit of the first preset range is f MAX .

[0047] Specifically, when the controller detects that the current compensation value for N consecutive cycles exceeds the first preset range, it reduces the preset factor until the current compensation value no longer exceeds the first preset range, thus preventing the current compensation value from continuously exceeding the compensation value safety boundary. N can be 3 to 5.

[0048] As can be seen from the above embodiments, if the current compensation value is not constrained, the current compensation value may exceed the withstand capability of the DC / DC converter power devices due to a sudden increase in ripple error or deviation in PI parameter setting, thereby causing output current distortion, loop oscillation, or even damage to the power devices. This embodiment limits the current compensation value by using a first preset range, clarifying the safety boundary of the current compensation signal. This ensures that the current compensation value is sufficient to offset the ripple while preventing it from exceeding the output capability and device tolerance range of the DC / DC converter, effectively preventing problems such as overcurrent, overvoltage, or output waveform distortion. At the same time, the limiting process does not weaken the core effect of ripple suppression. Under normal ripple conditions, the current compensation value is within the first preset range and can fully exert its offsetting effect; only in extreme and sudden scenarios is the limiting process used to protect system stability, achieving the dual goals of ripple suppression and system safety.

[0049] In one possible implementation, the specific implementation process of associating the actual value of the output current and the given value of the output current based on the same amplification factor in S102 includes: If the difference between the actual output current value and the given output current value is less than a preset difference threshold, then the actual output current value and the given output current value are correlated based on the same amplification factor.

[0050] In this embodiment, the preset difference threshold is a critical value that distinguishes between ripple-dominated operating conditions and large disturbance operating conditions. When the absolute value of the difference between the actual value of the output current and the given value is less than the preset difference threshold, it indicates that the system is in a steady state and the deviation is mainly caused by ripple; when the absolute value of the difference is greater than or equal to the preset difference threshold, it indicates that the system has experienced a large disturbance and current tracking needs to be prioritized.

[0051] Specifically, in this embodiment, the preset difference threshold can be dynamically adjusted based on the absolute value of the difference between the actual output current value and the given output current value. If the absolute value of the difference is less than a first value for M consecutive cycles, the initial preset difference threshold is decreased. If the absolute value of the difference is greater than a second value for M consecutive cycles, the initial preset difference threshold is increased. When the absolute value of the difference is between the first and second values ​​for M consecutive cycles, the current preset difference threshold remains unchanged. Here, the first value is less than the second value.

[0052] In one possible implementation, when the controller detects that the difference between the actual output current value of the previous cycle and the given output current value is not less than a preset difference threshold, while the difference between the actual output current value of the current cycle and the given output current value is less than the preset difference threshold, indicating a system operating condition shift from a large disturbance condition to a ripple-dominated condition, then when the current compensation value of the current cycle is obtained, the first preset range for limiting the current compensation value is linearly restored from zero to a pre-set compensation value safety boundary. When the controller detects that the difference between the actual output current value of the previous cycle and the given output current value is less than the preset difference threshold, while the difference between the actual output current value of the current cycle and the given output current value is not less than the preset difference threshold, indicating a system operating condition shift from a ripple-dominated condition to a large disturbance condition, then when the current compensation value of the current cycle is obtained, the first preset range for limiting the current compensation value is linearly reduced from the pre-set compensation value safety boundary to zero, avoiding current surges caused by sudden changes in the current compensation value and ensuring a smooth transition between operating conditions.

[0053] As can be seen from the above embodiments, the operation of a DC / DC converter not only involves a steady-state condition dominated by ripple, but also faces large disturbance conditions such as sudden load changes and large fluctuations in bus voltage. The key issue in these situations is current tracking error, not minute ripple. If high-gain correlation processing and compensation are still activated, the current compensation value may be superimposed on the large disturbance, leading to current loop instability and severe fluctuations in output current. Therefore, this embodiment distinguishes between the two operating conditions by setting a preset difference threshold. When the difference between the actual output current value and the given value is less than the preset difference threshold, it indicates a steady-state condition, and correlation gain processing and compensation are activated to focus on suppressing low-frequency ripple. When the difference is greater than the preset difference threshold, it indicates a dynamic large disturbance condition, so ripple optimization is paused to prioritize ensuring the dynamic response capability of the original current loop, quickly tracking the current setpoint, and avoiding interference from the compensation signal with the large disturbance regulation of the current loop.

[0054] Furthermore, as another preferred implementation, to avoid introducing excessive high-frequency noise and causing control instability when the fixed sampling bandwidth has low ripple, this embodiment also provides an adaptive sampling bandwidth adjustment method. This method does not require further modification of the hardware circuitry; instead, it dynamically adjusts the equivalent bandwidth within the controller using a digital filter. Specifically, this includes: The peak or effective value of the output current ripple is calculated in real time and used as the ripple amplitude. The ripple amplitude is compared with the preset difference threshold. When the ripple amplitude is greater than the preset difference threshold, it is determined that the current ripple is large and the real signal dominates. At this time, the software increases the equivalent cutoff frequency of the digital filter (for example, to 3.6KHz) to widen the equivalent sampling bandwidth, thereby obtaining more realistic ripple phase and amplitude information for use by the ripple suppression loop. When the ripple amplitude is less than the second threshold, it is determined that the current ripple is small and the noise impact is relatively significant. At this time, the software reduces the equivalent cutoff frequency of the digital filter (e.g., to 1.1kHz) to narrow the equivalent bandwidth, filter out high-frequency components such as switching noise and EMI interference, prevent the controller from outputting unnecessary correction values ​​due to noise, and avoid generating additional ripple. Through the above adaptive adjustment, this embodiment can accurately extract ripple characteristics and achieve effective compensation under high ripple conditions, while maintaining sampling stability under low ripple conditions, thus balancing ripple suppression effect and system noise robustness. The second amplitude is less than the preset difference threshold.

[0055] In one possible implementation, prior to S103, the method provided in this embodiment further includes: The output current setpoint I o_ref Subtract the actual value of the output current I o_fdb The output current difference is obtained. The output current difference is input into the second PI controller to obtain the current loop output value. f i .

[0056] In this embodiment, the generation logic of the original current loop output value is clarified. That is, the output current difference is first calculated and then input into the second PI controller to obtain the current loop output value, forming a dual-loop collaborative architecture of the second PI basic current loop and the first PI ripple compensation loop, which breaks through the limitation of traditional single-loop control in terms of dynamic response and low-frequency gain.

[0057] Specifically, in traditional single-loop control, the PI controller must simultaneously handle both current tracking and ripple suppression. If dynamic response is prioritized, the proportional gain needs to be increased, but this may result in insufficient low-frequency gain and poor ripple suppression. Conversely, if low-frequency ripple suppression is prioritized, the integral gain needs to be increased, but this sacrifices dynamic response speed, leading to tracking lag during load changes. This embodiment uses a second PI controller focused on basic current tracking. Its parameters can be tuned according to the dynamic response requirements of the DC / DC converter, ensuring that the current can quickly track the given value under scenarios such as load changes and bus voltage fluctuations, guaranteeing the basic operational stability of the system. The first PI controller focuses on ripple compensation, with parameters optimized for low-frequency ripple, increasing low-frequency gain to offset ripple. The dual-loop architecture has a clear division of labor and works collaboratively, without interfering with each other and complementing each other. Through superimposed compensation, it can significantly reduce output current ripple without affecting dynamic response. Furthermore, the dual-loop architecture is compatible with the existing control framework of DC / DC converters, requiring no reconstruction of the core control logic, only the addition of a compensation loop module, reducing the difficulty of modification and upgrade costs, and facilitating engineering application.

[0058] In one possible implementation, refer to Figure 4The specific implementation process of controlling the charging module based on the compensated current loop output value in S103 includes: Obtain the voltage loop output value of the charging module. f u ; Select the compensated current loop output value f i and the voltage loop output value f u The larger value in the range is taken as the target control variable Gf; The target control quantity Gf is used to generate a PWM (Pulse Width Modulation) signal to control the charging module.

[0059] In this embodiment, reference Figure 4 The voltage loop control process of the charging module is as follows: Obtain the actual output voltage value U of the charging module o_fdb ; Set the output voltage of the charging module to value U. o_ref Subtract the actual output voltage U o_fdb The voltage difference is obtained; The voltage difference is input to the third PI controller to obtain the voltage loop output value. f u .

[0060] After obtaining the voltage loop output value, the larger value between the compensated current loop output value and the voltage loop output value is selected as the target control quantity Gf. Then, the duty cycle is calculated using the target control quantity Gf, and the duty cycle is input into the modulation module. A periodic PWM signal is generated through the carrier comparison method, and the PWM signal is output to the DC / DC converter to control the on / off time of the power devices in the DC / DC converter, thereby achieving precise regulation of electrical energy.

[0061] As can be seen from the above embodiments, this embodiment adds the technical feature of selecting the larger value between the compensated current loop output value and the voltage loop output value to generate the PWM signal. When the voltage loop output value is greater than the compensated current loop output value, the voltage loop output is preferentially used to generate the PWM signal to ensure voltage stability and equipment safety; when the compensated current loop output value is better, the current loop output is used to balance ripple suppression and current stability. This achieves dual protection of voltage safety and ripple suppression.

[0062] It should be understood that the sequence number of each step in the above embodiments does not imply the order of execution. The execution order of each process should be determined by its function and internal logic, and should not constitute any limitation on the implementation process of the embodiments of the present invention.

[0063] The following are device embodiments of the present invention. For details not described in detail, please refer to the corresponding method embodiments described above.

[0064] Figure 5 A schematic diagram of the output ripple optimization device for a charging module provided in an embodiment of the present invention is shown. For ease of explanation, only the parts related to the embodiment of the present invention are shown, and are described in detail below: like Figure 5 As shown, the output ripple optimization device 100 of the charging module includes: Data acquisition module 110 is used to acquire the actual value of the output current and the setpoint value of the output current of the charging module; The current compensation value calculation module 120 is used to perform correlation processing on the actual value of the output current and the given value of the output current based on the same amplification factor to obtain the gain current difference, and calculate the current compensation value based on the gain current difference. The control module 130 is used to superimpose the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value, and control the charging module based on the compensated current loop output value.

[0065] In one possible implementation, the current compensation value calculation module 120 is specifically used for: Both the actual value of the output current and the given value of the output current are amplified by a preset factor; The gain current difference is obtained by subtracting the actual value of the output current from the amplified given value of the output current.

[0066] In one possible implementation, the current compensation value calculation module 120 is specifically used for: The gain current difference is input into the first PI controller to obtain the current compensation value.

[0067] In one possible implementation, the output ripple optimization device for the charging module further includes: A limiting module is used to limit the current compensation value using a first preset range; Accordingly, the control module includes: The current compensation value after the limiting process is superimposed on the current loop output value of the charging module to obtain the compensated current loop output value.

[0068] In one possible implementation, the current compensation value calculation module 120 is specifically used for: If the difference between the actual output current value and the given output current value is less than a preset difference threshold, then the actual output current value and the given output current value are correlated based on the same amplification factor.

[0069] In one possible implementation, the output ripple optimization device for the charging module further includes a current loop module for: The output current difference is obtained by subtracting the actual output current value from the given output current value. The output current difference is input into the second PI controller to obtain the current loop output value.

[0070] In one possible implementation, the control module is specifically used for: Obtain the voltage loop output value of the charging module; The larger of the compensated current loop output value and the voltage loop output value is selected as the target control variable; The target control quantity is used to generate a PWM signal to control the charging module.

[0071] Figure 6 This is a schematic diagram of the controller provided in an embodiment of the present invention. Figure 6 As shown, the controller 6 in this embodiment includes a processor 60, a memory 61, and a computer program 62 stored in the memory 61 and executable on the processor 60. When the processor 60 executes the computer program 62, it implements the steps in the above-described embodiments of the output ripple optimization method for each charging module, for example... Figure 2 Steps S101 to S103 are shown. Alternatively, when the processor 60 executes the computer program 62, it implements the functions of each module / unit in the above-described device embodiments, for example... Figure 5 The functions of modules 110 to 130 are shown.

[0072] For example, the computer program 62 can be divided into one or more modules / units, which are stored in the memory 61 and executed by the processor 60 to complete the present invention. The one or more modules / units can be a series of computer program instruction segments capable of performing a specific function, which describe the execution process of the computer program 62 in the controller 6.

[0073] The controller 6 can be a computing device such as a desktop computer, laptop, handheld computer, or cloud server. The controller 6 may include, but is not limited to, a processor 60 and a memory 61. Those skilled in the art will understand that... Figure 6 This is merely an example of controller 6 and does not constitute a limitation on controller 6. It may include more or fewer components than shown, or combine certain components, or different components. For example, the controller may also include input / output devices, network access devices, buses, etc.

[0074] The processor 60 may be a Central Processing Unit (CPU), or other general-purpose processors, digital signal processors (DSPs), application-specific integrated circuits (ASICs), field-programmable gate arrays (FPGAs), or other programmable logic devices, discrete gate or transistor logic devices, discrete hardware components, etc. A general-purpose processor may be a microprocessor or any conventional processor.

[0075] The memory 61 can be an internal storage unit of the controller 6, such as a hard disk or memory of the controller 6. The memory 61 can also be an external storage device of the controller 6, such as a plug-in hard disk, Smart Media Card (SMC), Secure Digital (SD) card, or Flash Card equipped on the controller 6. Furthermore, the memory 61 can include both internal storage units and external storage devices of the controller 6. The memory 61 is used to store the computer program and other programs and data required by the controller. The memory 61 can also be used to temporarily store data that has been output or will be output.

[0076] Those skilled in the art will clearly understand that, for the sake of convenience and brevity, the above-described division of functional units and modules is merely an example. In practical applications, the above functions can be assigned to different functional units and modules as needed, that is, the internal structure of the device can be divided into different functional units or modules to complete all or part of the functions described above. The functional units and modules in the embodiments can be integrated into one processing unit, or each unit can exist physically separately, or two or more units can be integrated into one unit. The integrated unit can be implemented in hardware or as a software functional unit. Furthermore, the specific names of the functional units and modules are only for easy differentiation and are not intended to limit the scope of protection of this application. The specific working process of the units and modules in the above system can be referred to the corresponding process in the foregoing method embodiments, and will not be repeated here.

[0077] In the above embodiments, the descriptions of each embodiment have different focuses. For parts that are not described in detail or recorded in a certain embodiment, please refer to the relevant descriptions of other embodiments.

[0078] Those skilled in the art will recognize that the units and algorithm steps of the various examples described in conjunction with the embodiments disclosed herein can be implemented in electronic hardware, or a combination of computer software and electronic hardware. Whether these functions are implemented in hardware or software depends on the specific application and design constraints of the technical solution. Those skilled in the art can use different methods to implement the described functions for each specific application, but such implementations should not be considered beyond the scope of this invention.

[0079] In the embodiments provided by this invention, it should be understood that the disclosed devices / controllers and methods can be implemented in other ways. For example, the device / controller embodiments described above are merely illustrative. For instance, the division of modules or units is only a logical functional division, and in actual implementation, there may be other division methods. For example, multiple units or components may be combined or integrated into another system, or some features may be ignored or not executed. Furthermore, the coupling or direct coupling or communication connection shown or discussed may be through some interfaces; the indirect coupling or communication connection between devices or units may be electrical, mechanical, or other forms.

[0080] The units described as separate components may or may not be physically separate. The components shown as units may or may not be physical units; that is, they may be located in one place or distributed across multiple network units. Some or all of the units can be selected to achieve the purpose of this embodiment according to actual needs.

[0081] Furthermore, the functional units in the various embodiments of the present invention can be integrated into one processing unit, or each unit can exist physically separately, or two or more units can be integrated into one unit. The integrated unit can be implemented in hardware or as a software functional unit.

[0082] If the integrated module / unit is implemented as a software functional unit and sold or used as an independent product, it can be stored in a computer-readable storage medium. Based on this understanding, all or part of the processes in the above embodiments of the present invention can also be implemented by a computer program instructing related hardware. The computer program can be stored in a computer-readable storage medium, and when executed by a processor, it can implement the steps of the above embodiments of the output ripple optimization method for each charging module. The computer program includes computer program code, which can be in the form of source code, object code, executable files, or certain intermediate forms. The computer-readable medium can include: any entity or device capable of carrying the computer program code, a recording medium, a USB flash drive, a portable hard drive, a magnetic disk, an optical disk, a computer memory, a read-only memory (ROM), a random access memory (RAM), an electrical carrier signal, a telecommunication signal, and a software distribution medium, etc.

[0083] The above-described embodiments are only used to illustrate the technical solutions of the present invention, and are not intended to limit it. Although the present invention has been described in detail with reference to the foregoing embodiments, those skilled in the art should understand that modifications can still be made to the technical solutions described in the foregoing embodiments, or equivalent substitutions can be made to some of the technical features. Such modifications or substitutions do not cause the essence of the corresponding technical solutions to deviate from the spirit and scope of the technical solutions of the embodiments of the present invention, and should all be included within the protection scope of the present invention.

Claims

1. A method for optimizing the output ripple of a charging module, characterized in that, include: Obtain the actual value and the setpoint value of the output current of the charging module; The actual value of the output current and the given value of the output current are correlated based on the same amplification factor to obtain the gain current difference, and the current compensation value is calculated based on the gain current difference. The current compensation value is superimposed on the current loop output value of the charging module to obtain the compensated current loop output value, and the charging module is controlled based on the compensated current loop output value.

2. The method for optimizing the output ripple of a charging module according to claim 1, characterized in that, The correlation processing between the actual value of the output current and the given value of the output current based on the same amplification factor includes: Both the actual value of the output current and the given value of the output current are amplified by a preset factor; The gain current difference is obtained by subtracting the actual value of the output current from the amplified given value of the output current.

3. The method for optimizing the output ripple of a charging module according to claim 1, characterized in that, The step of calculating the current compensation value based on the gain current difference includes: The gain current difference is input into the first PI controller to obtain the current compensation value.

4. The method for optimizing the output ripple of a charging module according to claim 1, characterized in that, After calculating the current compensation value based on the gain current difference, the method further includes: The current compensation value is limited using a first preset range; Accordingly, the step of superimposing the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value includes: The current compensation value after the limiting process is superimposed on the current loop output value of the charging module to obtain the compensated current loop output value.

5. The method for optimizing the output ripple of a charging module according to any one of claims 1 to 4, characterized in that, The correlation processing between the actual value of the output current and the given value of the output current based on the same amplification factor includes: If the difference between the actual output current value and the given output current value is less than a preset difference threshold, then the actual output current value and the given output current value are correlated based on the same amplification factor.

6. The method for optimizing the output ripple of a charging module according to claim 1, characterized in that, Before adding the current compensation value to the current loop output value of the charging module to obtain the compensated current loop output value, the method further includes: The output current difference is obtained by subtracting the actual output current value from the given output current value. The output current difference is input into the second PI controller to obtain the current loop output value.

7. The method for optimizing the output ripple of a charging module according to claim 1, characterized in that, The control of the charging module based on the compensated current loop output value includes: Obtain the voltage loop output value of the charging module; The larger of the compensated current loop output value and the voltage loop output value is selected as the target control variable; The target control quantity is used to generate a PWM signal to control the charging module.

8. A device for optimizing the output ripple of a charging module, characterized in that, include: The data acquisition module is used to acquire the actual value and the setpoint value of the output current of the charging module; The current compensation value calculation module is used to correlate the actual value of the output current and the given value of the output current based on the same amplification factor to obtain the gain current difference, and calculate the current compensation value based on the gain current difference. The control module is used to superimpose the current compensation value with the current loop output value of the charging module to obtain the compensated current loop output value, and control the charging module based on the compensated current loop output value.

9. A controller comprising a memory, a processor, and a computer program stored in the memory and executable on the processor, characterized in that, When the processor executes the computer program, it implements the steps of the output ripple optimization method for the charging module as described in any one of claims 1 to 7.

10. A charging device, characterized in that, Includes the controller as described in claim 9.

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