A filter optimization-based power dual-mode communication anti-interference method and system

Abstract

The application relates to the technical field of electric power communication, and discloses an anti-interference method and system for electric power dual-mode communication based on filter optimization, which comprises the following steps: performing frequency band separation processing on a digital mixed signal to obtain a carrier frequency band signal and a wireless frequency band signal; performing multi-stage notch filter optimization on the carrier frequency band signal according to interference frequency point distribution characteristics to obtain a carrier purification signal; performing multi-path time delay estimation and fractional interval equalization on the wireless frequency band signal to obtain a wireless purification signal; respectively performing carrier coherent demodulation and wireless coherent demodulation on the carrier purification signal and the wireless purification signal to obtain a carrier demodulation soft bit sequence and a wireless demodulation soft bit sequence; performing signal-to-noise ratio weighted combination on bit values of the carrier demodulation soft bit sequence and bit values of the wireless demodulation soft bit sequence to obtain a combined soft bit value; and performing polarity discrimination mapping on the combined soft bit value to obtain an anti-interference output bit stream; and the application can improve the anti-interference efficiency of electric power dual-mode communication.

Description

Technical Field

[0001] This invention relates to the field of power communication technology, and in particular to a method and system for anti-interference of dual-mode power communication based on filter optimization. Background Technology

[0002] Existing power dual-mode communication processing schemes only perform simple frequency band division for mixed signals, which cannot accurately identify randomly distributed narrowband interference frequency points within the carrier channel. The filtering process only adopts a single-stage filtering structure with fixed parameters, which is difficult to match the dynamically changing interference bandwidth, resulting in high residual noise in interference suppression. At the same time, the wireless frequency band signals do not undergo refined multipath delay clustering analysis, and the equalization tap parameters remain unchanged, which cannot adapt to the signal distortion caused by changes in multipath delay distribution. The purification effect of the two signals has obvious shortcomings.

[0003] Existing solutions only perform simple hard bit combining on the two bit paths after demodulation, without considering the real-time signal-to-noise ratio of the channel for soft bit weighting fusion. Bit decision-making uses a fixed threshold to determine polarity, which cannot adapt to signal amplitude fluctuations in dynamic noise environments. Consequently, the communication error rate indicators fail to meet the transmission requirements of complex power scenarios. Therefore, improving the overall anti-interference processing performance of dual-mode power communication systems has become an urgent problem to be solved. Summary of the Invention

[0004] This invention provides a power dual-mode communication anti-interference method and system based on filter optimization to solve the problems mentioned in the background art.

[0005] To achieve the above objectives, this invention provides a power line dual-mode communication anti-interference method based on filter optimization, comprising:

[0006] D1. Perform frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the wireless frequency band signal of the power dual-mode communication;

[0007] D2. Based on the interference frequency distribution characteristics of the carrier frequency band signal, perform multi-level notch filtering optimization on the carrier frequency band signal to obtain the carrier purified signal for the power dual-mode communication;

[0008] D3. Perform multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and perform fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal of the power dual-mode communication.

[0009] D4. Perform carrier coherent demodulation and wireless coherent demodulation on the carrier purification signal and the wireless purification signal respectively to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence of the power dual-mode communication.

[0010] D5. The bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence are combined using a signal-to-noise ratio weighted sum to obtain the combined soft bit value of the power dual-mode communication.

[0011] D6. Perform polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication.

[0012] In a preferred embodiment, the step of performing frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the radio frequency band signal of the power dual-mode communication includes:

[0013] The digital hybrid signal of the power dual-mode communication is acquired, and the digital hybrid signal is windowed and framed in the time domain to obtain the frame sequence of the digital hybrid signal;

[0014] Based on the frame sequence, frequency analysis and conversion are performed on the digital mixed signal to obtain the frequency domain complex spectrum sequence of the digital mixed signal;

[0015] Based on the spectral line energy distribution in the frequency domain complex spectrum sequence, extract the carrier band energy centroid and the wireless band energy centroid of the digital mixed signal;

[0016] Based on the energy centroid of the carrier frequency band and the energy centroid of the wireless frequency band, carrier passband mask extraction and wireless passband mask extraction are performed on the frequency domain complex spectrum sequence to obtain the carrier frequency band signal and wireless frequency band signal of the power dual-mode communication.

[0017] In a preferred embodiment, the step of performing multi-level notch filtering optimization on the carrier frequency band signal based on the interference frequency distribution characteristics of the carrier frequency band signal to obtain the carrier-cleaned signal for the power dual-mode communication includes:

[0018] A sliding window spectral energy accumulation process is performed on the carrier frequency band signal to obtain the spectral energy accumulation sequence of the carrier frequency band signal;

[0019] Based on the local extreme value distribution of the accumulated spectral energy sequence, determine the peak position of the accumulated spectral energy and the frequency width of the accumulated spectral energy sequence.

[0020] The peak position of the spectral energy is taken as the interference frequency point position of the carrier frequency band signal, and the frequency width of the spectral energy is taken as the interference frequency point bandwidth of the carrier frequency band signal.

[0021] Based on the location and bandwidth of the interference frequency point, the stopband configuration parameters of the carrier frequency band signal are generated;

[0022] Based on the stopband configuration parameters, the carrier frequency band signal is subjected to step-by-step notch filtering to obtain the carrier cleaned signal for the power dual-mode communication.

[0023] In a preferred embodiment, the step of performing stepwise notch filtering on the carrier frequency band signal based on the stopband configuration parameters to obtain the carrier cleaned signal for the power dual-mode communication includes:

[0024] Based on the stopband configuration parameters, amplitude suppression is performed on the frequency domain spectral lines corresponding to the interference frequency points in the carrier frequency band signal to obtain the first-level clean signal of the carrier frequency band signal;

[0025] Amplitude suppression is performed on the frequency domain spectral line at the next interference frequency point in the first-level purified signal to obtain the second-level purified signal of the carrier frequency band signal;

[0026] The operation of amplitude suppression of the frequency domain spectral line at the next interference frequency point in the current level of the clean signal is repeated until amplitude suppression is completed for the frequency domain spectral lines at all interference frequency points in the carrier frequency band signal, and the last level of clean signal is used as the carrier clean signal for the power dual-mode communication.

[0027] In a preferred embodiment, the step of performing multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and performing fractional-interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless cleanup signal for the power dual-mode communication, includes:

[0028] Energy envelope extraction is performed on the wireless frequency band signal to obtain the energy envelope sequence of the wireless frequency band signal;

[0029] Initial cluster boundary labeling is performed on the amplitude transition edges in the energy envelope sequence to obtain the initial cluster boundary label of the energy envelope sequence;

[0030] Based on the initial cluster boundary markers, the time delay taps in the energy envelope sequence are grouped and merged to obtain the multipath cluster grouping results of the wireless band signal;

[0031] Based on the multipath cluster grouping results, the multipath interference delay distribution of the wireless frequency band signal is generated;

[0032] Based on the cluster delay range in the multipath interference delay distribution, the fractional interval equalization tap coefficients of the wireless band signal are reconfigured to obtain the reconfigured tap coefficient sequence of the wireless band signal.

[0033] Based on the recombined tap coefficient sequence, the wireless frequency band signal is subjected to fractional interval equalization filtering to obtain the wireless purification signal for the power dual-mode communication.

[0034] In a preferred embodiment, the step of grouping and merging the time delay taps in the energy envelope sequence based on the initial cluster boundary markers to obtain the multipath cluster grouping result of the energy envelope sequence includes:

[0035] Based on the initial cluster boundary markers, determine the positions of the candidate cluster heads and tails in the energy envelope sequence;

[0036] Based on the candidate cluster head position and the candidate cluster tail position, extract the time delay tap subsequence of the candidate cluster in the energy envelope sequence;

[0037] The intra-cluster energy centroid is estimated for the time delay tap subsequence to obtain the time delay centroid position of the candidate cluster;

[0038] Based on the time delay centroid position of the candidate cluster, the inter-cluster spacing of adjacent candidate clusters is determined, and adjacent candidate clusters with an inter-cluster spacing less than a preset spacing threshold are merged into the same multipath cluster to obtain the multipath cluster grouping result of the energy envelope sequence.

[0039] In a preferred embodiment, the step of performing carrier coherent demodulation and wireless coherent demodulation on the carrier cleanup signal and the wireless cleanup signal, respectively, to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence for the power dual-mode communication, includes:

[0040] Carrier phase recovery is performed on the carrier cleanup signal to obtain the carrier in-phase component and carrier quadrature component of the carrier cleanup signal;

[0041] Symbol decision metric extraction is performed on the in-phase carrier component and the quadrature carrier component to obtain the carrier decision metric value of the carrier cleanup signal, and the carrier soft bit value of the carrier cleanup signal is determined based on the carrier decision metric value.

[0042] Carrier phase recovery is performed on the wireless purification signal to obtain the wireless in-phase component and the wireless quadrature component of the wireless purification signal.

[0043] Symbol decision metric extraction is performed on the wireless in-phase component and the wireless quadrature component to obtain the wireless decision metric value of the wireless decontamination signal, and the wireless soft bit value of the wireless decontamination signal is determined based on the wireless decision metric value.

[0044] The carrier soft bit value and the wireless soft bit value are time-sequentially arranged to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence for the power dual-mode communication.

[0045] In a preferred embodiment, the step of performing signal-to-noise ratio weighted combining of the bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence to obtain the combined soft bit value for the power dual-mode communication includes:

[0046] The carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence are aligned at the bit level to obtain the aligned carrier soft bit sequence and the aligned wireless soft bit sequence for the power dual-mode communication.

[0047] The soft bit amplitudes of the aligned carrier soft bit sequence and the aligned wireless soft bit sequence are extracted respectively to obtain the carrier soft bit amplitude and wireless soft bit amplitude of the power dual-mode communication.

[0048] The combined soft-bit value of the power dual-mode communication is calculated using the aligned carrier soft-bit sequence, the aligned radio soft-bit sequence, the carrier soft-bit amplitude, and the radio soft-bit amplitude. The formula for calculating the combined soft-bit value is as follows:

[0049] ;

[0050] in, For the merged soft bit value, The soft bit values ​​of the aligned carrier soft bit sequence. The soft bit values ​​of the aligned wireless soft bit sequence. The carrier soft bit amplitude, The amplitude of the wireless soft bit is mentioned.

[0051] In a preferred embodiment, the step of performing polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication includes:

[0052] A time-series sliding truncation is performed on the merged soft bit value to obtain a local data window of the merged soft bit value;

[0053] The dynamic decision boundary for the merged soft bit value is obtained based on the degree of data dispersion within the local data window.

[0054] Based on the dynamic decision boundary, the sign attribute of the merged soft bit value is determined to obtain the preliminary logical sequence of the merged soft bit value;

[0055] The preliminary logic sequence is logically smoothed to obtain the anti-interference output bit stream of the power dual-mode communication.

[0056] To address the aforementioned problems, this invention also provides a power dual-mode communication anti-interference system based on filter optimization, the system comprising:

[0057] The frequency band separation module is used to perform frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the wireless frequency band signal of the power dual-mode communication;

[0058] The carrier filtering module is used to perform multi-level notch filtering optimization on the carrier frequency band signal according to the interference frequency point distribution characteristics of the carrier frequency band signal to obtain the carrier cleaned signal of the power dual-mode communication.

[0059] A wireless equalization module is used to perform multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and to perform fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal of the power dual-mode communication.

[0060] The coherent demodulation module is used to perform carrier coherent demodulation and wireless coherent demodulation on the carrier cleanup signal and the wireless cleanup signal respectively to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence of the power dual-mode communication.

[0061] A soft bit weighting module is used to perform signal-to-noise ratio weighted merging of the bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence to obtain the merged soft bit value of the power dual-mode communication.

[0062] The bit decision module is used to perform polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication.

[0063] Compared with the prior art, the present invention has the following beneficial effects:

[0064] 1. This invention distinguishes between carrier and wireless signals by frequency band separation. It performs multi-level notch filtering optimization on the carrier frequency band signal, accurately locates the interference frequency and bandwidth based on the real-time spectrum energy extreme value, and suppresses the interference spectrum line step by step. At the same time, it performs multipath delay cluster division and fractional interval equalization filtering on the wireless frequency band signal, which can simultaneously eliminate narrowband interference of power line carrier and multipath distortion of wireless channel. After independent purification of the two signals, the noise floor is significantly reduced, the effective signal carrying power is improved, and the signal purity at the communication receiving end is greatly improved.

[0065] 2. This invention outputs two soft bit sequences through coherent demodulation, and completes the fusion of dual-channel soft information by relying on bit alignment and amplitude weighting formula. Combined with dynamic decision boundary and logical smoothing processing, the output bit stream fully utilizes the signal-to-noise ratio advantages of the carrier and wireless dual-mode channels to achieve complementary merging of information, improve the reliability of bit discrimination, effectively reduce the communication bit error rate, and complete the closed loop of the overall power dual-mode communication anti-interference processing flow. The communication transmission stability and data reception accuracy are improved simultaneously. Attached Figure Description

[0066] Figure 1 This is a flowchart illustrating an anti-interference method for power dual-mode communication based on filter optimization, provided in an embodiment of the present invention.

[0067] Figure 2 A functional block diagram of a power dual-mode communication anti-interference system based on filter optimization is provided in an embodiment of the present invention.

[0068] The realization of the objective, functional features and advantages of the present invention will be further explained in conjunction with the embodiments and with reference to the accompanying drawings. Detailed Implementation

[0069] It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.

[0070] This application provides a power line dual-mode communication anti-interference method based on filter optimization. The executing entity of this filter-optimized power line dual-mode communication anti-interference method includes, but is not limited to, at least one of the following electronic devices that can be configured to execute the method provided in this application: a server, a terminal, etc. In other words, the filter-optimized power line dual-mode communication anti-interference method can be executed by software or hardware installed on a terminal device or a server device. The server includes, but is not limited to, a single server, a server cluster, a cloud server, or a cloud server cluster. The server can be an independent server or a cloud server that provides basic cloud computing services such as cloud services, cloud databases, cloud computing, cloud functions, cloud storage, network services, cloud communication, middleware services, domain name services, security services, content delivery networks (CDNs), and big data and artificial intelligence platforms.

[0071] Reference Figure 1 The diagram shown is a flowchart illustrating a power line dual-mode communication anti-interference method based on filter optimization according to an embodiment of the present invention. In this embodiment, the power line dual-mode communication anti-interference method based on filter optimization includes:

[0072] D1. Perform frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the wireless frequency band signal of the power dual-mode communication;

[0073] In this embodiment of the invention, the step of performing frequency band separation processing on the digital hybrid signal of power dual-mode communication to obtain the carrier frequency band signal and the radio frequency band signal of the power dual-mode communication includes:

[0074] The digital hybrid signal of the power dual-mode communication is acquired, and the digital hybrid signal is windowed and framed in the time domain to obtain the frame sequence of the digital hybrid signal;

[0075] Based on the frame sequence, frequency analysis and conversion are performed on the digital mixed signal to obtain the frequency domain complex spectrum sequence of the digital mixed signal;

[0076] Based on the spectral line energy distribution in the frequency domain complex spectrum sequence, extract the carrier band energy centroid and the wireless band energy centroid of the digital mixed signal;

[0077] Based on the energy centroid of the carrier frequency band and the energy centroid of the wireless frequency band, carrier passband mask extraction and wireless passband mask extraction are performed on the frequency domain complex spectrum sequence to obtain the carrier frequency band signal and wireless frequency band signal of the power dual-mode communication.

[0078] The complete digital mixed signal of dual-mode power communication is acquired. A time-domain window function of fixed length is applied to the complete digital mixed signal of dual-mode power communication to complete the signal truncation operation. The continuous and complete digital mixed signal of dual-mode power communication is divided into multiple independent short-time signal segments. All short-time signal segments are integrated to form a frame sequence of the digital mixed signal. Each short-time signal segment in the frame sequence retains the complete time-domain signal characteristics of the original digital mixed signal.

[0079] For each independent short-time signal segment within the frame sequence, a full-domain frequency decomposition and transformation operation is performed segment by segment. Each short-time signal segment carrying only time-domain information is completely converted into frequency-domain data that simultaneously carries amplitude and phase information. The frequency-domain data obtained from the conversion of all short-time signal segments are arranged and integrated in the original arrangement order of the frame sequence to form the frequency-domain complex spectrum sequence of the digital mixed signal. Each data unit within the frequency-domain complex spectrum sequence corresponds one-to-one with the complete frequency-domain information of each short-time signal segment within the frame sequence.

[0080] The energy values ​​of all data units within the complex spectrum sequence in the frequency domain are traversed. A global statistical analysis is performed on all energy values ​​to distinguish between all energy values ​​concentrated in the carrier frequency interval and all energy values ​​concentrated in the wireless frequency interval. The overall distribution center positions of all energy values ​​in the carrier frequency interval and the wireless frequency interval are statistically analyzed respectively. The energy distribution center position in the carrier frequency interval is defined as the energy centroid of the carrier band of the digital mixed signal, and the energy distribution center position in the wireless frequency interval is defined as the energy centroid of the wireless band of the digital mixed signal. The energy centroid of the carrier band and the energy centroid of the wireless band can accurately distinguish the frequency interval boundaries of the two types of signals.

[0081] Using the frequency range where the energy centroid of the carrier band is located as the delineation benchmark, all spectral line data belonging to the carrier communication band are selected from within the complex spectrum sequence in the frequency domain. All selected carrier band spectral line data are fully preserved, while spectral line data corresponding to other bands are removed. The fully preserved carrier band spectral line data are combined to form a carrier passband mask. Using the frequency range where the energy centroid of the wireless band is located as the delineation benchmark, all spectral line data belonging to the wireless communication band are selected from within the complex spectrum sequence in the frequency domain. All selected wireless band spectral line data... Complete preservation processing is performed, while all spectral data corresponding to other frequency bands are removed. The completely preserved wireless frequency band spectral data is combined to form a wireless passband mask. The carrier passband mask is then overlaid onto the complete frequency domain complex spectrum sequence to complete the data extraction operation. The extracted complete signal data containing only carrier frequency band information is the carrier frequency band signal of the power dual-mode communication. The wireless passband mask is then overlaid onto the complete frequency domain complex spectrum sequence to complete the data extraction operation. The extracted complete signal data containing only wireless frequency band information is the wireless frequency band signal of the power dual-mode communication.

[0082] The beneficial effects are that by relying on time-domain windowing and framing operations to split continuous mixed signals, the spectral aliasing problem caused by long-term signal frequency domain conversion is avoided. Based on the complete frequency domain complex spectrum sequence, the energy centroids of the two types of signals are statistically analyzed to complete the accurate division of frequency band boundaries. By relying on the corresponding passband mask to separate the two types of frequency band signals, the original effective signal components of the carrier frequency band signal and the wireless frequency band signal can be completely preserved. The mutual spectral crosstalk between the two types of frequency bands is completely isolated. The dual-mode signal is completely split from the signal processing front end, providing a clean and interference-free basic signal for subsequent carrier-side multi-level notch filtering optimization and wireless-side multipath delay estimation processing. This reduces the noise processing pressure of the back-end anti-interference processing stage and improves the overall signal processing accuracy of dual-mode communication.

[0083] D2. Based on the interference frequency distribution characteristics of the carrier frequency band signal, perform multi-level notch filtering optimization on the carrier frequency band signal to obtain the carrier purified signal for the power dual-mode communication;

[0084] In this embodiment of the invention, the step of performing multi-level notch filtering optimization on the carrier frequency band signal based on the interference frequency distribution characteristics of the carrier frequency band signal to obtain the carrier cleaned signal for the power dual-mode communication includes:

[0085] A sliding window spectral energy accumulation process is performed on the carrier frequency band signal to obtain the spectral energy accumulation sequence of the carrier frequency band signal;

[0086] Based on the local extreme value distribution of the accumulated spectral energy sequence, determine the peak position of the accumulated spectral energy and the frequency width of the accumulated spectral energy sequence.

[0087] The peak position of the spectral energy is taken as the interference frequency point position of the carrier frequency band signal, and the frequency width of the spectral energy is taken as the interference frequency point bandwidth of the carrier frequency band signal.

[0088] Based on the location and bandwidth of the interference frequency point, the stopband configuration parameters of the carrier frequency band signal are generated;

[0089] Based on the stopband configuration parameters, the carrier frequency band signal is subjected to step-by-step notch filtering to obtain the carrier cleaned signal for the power dual-mode communication.

[0090] The step of performing step-by-step notch filtering on the carrier frequency band signal based on the stopband configuration parameters to obtain the carrier cleaned signal for the power dual-mode communication includes:

[0091] Based on the stopband configuration parameters, amplitude suppression is performed on the frequency domain spectral lines corresponding to the interference frequency points in the carrier frequency band signal to obtain the first-level clean signal of the carrier frequency band signal;

[0092] Amplitude suppression is performed on the frequency domain spectral line at the next interference frequency point in the first-level purified signal to obtain the second-level purified signal of the carrier frequency band signal;

[0093] The operation of amplitude suppression of the frequency domain spectral line at the next interference frequency point in the current level of the clean signal is repeated until amplitude suppression is completed for the frequency domain spectral lines at all interference frequency points in the carrier frequency band signal, and the last level of clean signal is used as the carrier clean signal for the power dual-mode communication.

[0094] A continuously moving fixed-length window structure is selected to completely cover the entire frequency domain spectrum of the carrier frequency band signal. The window moves continuously along the frequency axis according to a fixed step value. Each time the window completes a stop, the energy values ​​corresponding to all spectral lines within the window are collected and superimposed and accumulated. After each movement and accumulation, an independent set of energy statistics results is generated. The energy statistics results generated during all window movements are arranged and integrated in the order of window movement to form the spectral energy accumulation sequence of the carrier frequency band signal. Each set of data in the spectral energy accumulation sequence corresponds to the total energy after continuous superposition of the corresponding frequency interval.

[0095] The entire data unit within the spectrum energy accumulation sequence is traversed. Each continuous local data segment within the spectrum energy accumulation sequence is extracted sequentially for numerical comparison and screening. The point in each local data segment where the value is higher than all adjacent data units is located. This point is marked as the spectrum energy peak position. The number of all continuous frequency points crossed by the energy values ​​on both sides of each peak position as they fall back to the stable baseline value is counted. The overall frequency range corresponding to all crossed frequency points is defined as the spectrum energy frequency width. The spectrum energy peak position and the spectrum energy frequency width correspond one-to-one with the frequency range of each energy abnormal bulge.

[0096] Each peak position of the spectral energy obtained from the screening is directly defined as the location of the interference frequency point inside the carrier frequency band signal. The spectral energy frequency width generated by matching the peak position is directly defined as the interference frequency point bandwidth corresponding to the interference frequency point location. Each set of mutually matching interference frequency point locations and interference frequency point bandwidths completely corresponds to an independent narrowband interference spectrum interval.

[0097] Retrieve the location and bandwidth of each matching interference frequency point, and set corresponding frequency band blocking constraints according to the frequency center point and frequency range of interference coverage for each interference. Integrate and summarize the frequency band blocking constraints corresponding to all interferences to form complete stopband configuration parameters. The stopband configuration parameters completely record the blocking center frequency and blocking coverage range corresponding to each interference.

[0098] Retrieve complete stopband configuration parameters, locate all frequency domain spectral lines corresponding to the first interference frequency point within the carrier frequency band signal, perform uniform attenuation and suppression processing on the signal amplitude of this part of the frequency domain spectral lines, and keep the original amplitude of the frequency domain spectral lines in the other interference-free frequency range unchanged. After completing this amplitude suppression, the first-level clean signal of the carrier frequency band signal is generated.

[0099] Retrieve complete stopband configuration parameters, locate all frequency domain spectral lines corresponding to the next interference frequency point immediately following the first interference frequency point within the first-level purified signal, perform uniform attenuation suppression processing on the signal amplitude of this part of the frequency domain spectral lines, and maintain the current amplitude state of the frequency domain spectral lines in other frequency ranges without modification. After completing this amplitude suppression, generate the second-level purified signal of the carrier frequency band signal.

[0100] Following the order of interference frequency points recorded by the stopband configuration parameters, a complete amplitude suppression operation is performed on the frequency domain spectral line corresponding to the next interference frequency point in the current level of clean signal that has not undergone amplitude suppression processing. After each round of amplitude suppression operation, a new level of clean signal is generated. This process is continuously repeated until all frequency domain spectral lines corresponding to all interference frequency points recorded by the stopband configuration parameters have completed amplitude attenuation suppression operations. After the loop terminates, the latest generated last-level clean signal is directly determined as the carrier clean signal of the power dual-mode communication.

[0101] The beneficial effects are as follows: relying on the accumulation of spectral energy through a sliding window, the energy characteristics of persistent narrowband interference within the carrier frequency band are fully captured; relying on local extreme value distribution, the frequency position and coverage bandwidth corresponding to each interference point are accurately locked; matching stopband configuration parameters are generated based on the actual distribution of interference; and multi-level point-by-point notch filtering is used to suppress the spectral amplitude corresponding to all interference frequency points step by step. This can completely eliminate various types of randomly distributed narrowband interference in the power line carrier channel, retain the effective communication signal energy within the carrier frequency band to the greatest extent, significantly reduce the residual interference noise level within the carrier signal, improve the purity of the carrier branch signal, reduce signal distortion caused by noise in the subsequent coherent demodulation stage, and stabilize the data accuracy of the soft bit sequence output by the carrier branch demodulation.

[0102] D3. Perform multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and perform fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal of the power dual-mode communication.

[0103] In this embodiment of the invention, the step of performing multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and performing fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless cleanup signal for the power dual-mode communication, includes:

[0104] Energy envelope extraction is performed on the wireless frequency band signal to obtain the energy envelope sequence of the wireless frequency band signal;

[0105] Initial cluster boundary labeling is performed on the amplitude transition edges in the energy envelope sequence to obtain the initial cluster boundary label of the energy envelope sequence;

[0106] Based on the initial cluster boundary markers, the time delay taps in the energy envelope sequence are grouped and merged to obtain the multipath cluster grouping results of the wireless band signal;

[0107] Based on the multipath cluster grouping results, the multipath interference delay distribution of the wireless frequency band signal is generated;

[0108] Based on the cluster delay range in the multipath interference delay distribution, the fractional interval equalization tap coefficients of the wireless band signal are reconfigured to obtain the reconfigured tap coefficient sequence of the wireless band signal.

[0109] Based on the recombined tap coefficient sequence, the wireless frequency band signal is subjected to fractional interval equalization filtering to obtain the wireless purification signal for the power dual-mode communication.

[0110] The step of grouping and merging the time delay taps in the energy envelope sequence based on the initial cluster boundary markers to obtain the multipath cluster grouping result of the energy envelope sequence includes:

[0111] Based on the initial cluster boundary markers, determine the positions of the candidate cluster heads and tails in the energy envelope sequence;

[0112] Based on the candidate cluster head position and the candidate cluster tail position, extract the time delay tap subsequence of the candidate cluster in the energy envelope sequence;

[0113] The intra-cluster energy centroid is estimated for the time delay tap subsequence to obtain the time delay centroid position of the candidate cluster;

[0114] Based on the time delay centroid position of the candidate cluster, the inter-cluster spacing of adjacent candidate clusters is determined, and adjacent candidate clusters with an inter-cluster spacing less than a preset spacing threshold are merged into the same multipath cluster to obtain the multipath cluster grouping result of the energy envelope sequence.

[0115] Complete time-domain amplitude data of the wireless frequency band signal is collected. The signal energy value corresponding to each time delay point is read point by point along the signal time delay dimension. The energy values ​​corresponding to all time delay points are arranged in the order of time delay to form a continuous fluctuating energy change curve. After recording all the point values ​​of the curve, they are integrated to form the energy envelope sequence of the wireless frequency band signal. Each data unit in the energy envelope sequence corresponds to the signal energy magnitude of a single time delay point.

[0116] The energy values ​​of adjacent data units are compared segment by segment along the overall time delay arrangement direction of the energy envelope sequence to identify the boundary points where the energy values ​​inside the sequence rise or fall rapidly. A unique identifier is added to each boundary point where the values ​​change drastically to complete the interval division. All identifiers are uniformly summarized and arranged to form the initial cluster boundary marker of the energy envelope sequence. The initial cluster boundary marker can completely divide each independent energy fluctuation interval within the energy envelope sequence.

[0117] Read all interval segmentation points recorded in the initial cluster boundary marker. Use each group of adjacent boundary points as the start and end points of the interval to lock the corresponding data interval. Define the data corresponding to all time delay points contained in the interval as time delay taps. Divide all time delay taps in the same interval into the same group to complete the preliminary classification. After the preliminary classification is completed, the multipath cluster grouping result of the wireless frequency band signal is obtained as the preliminary data. Then, according to the adjacent cluster merging rule, the secondary integration process is completed to obtain the final grouping result.

[0118] Each starting point of the interval marked by the initial cluster boundary marker is taken as the candidate cluster head position, and each ending point of the interval marked by the initial cluster boundary marker is taken as the candidate cluster tail position. Each set of matching candidate cluster head positions and candidate cluster tail positions corresponds to an independent signal energy fluctuation interval.

[0119] Using the matching candidate cluster head position and candidate cluster tail position as the start and end boundaries of the extraction, all time delay tap corresponding data contained in the interval are completely extracted from the complete energy envelope sequence. All the extracted data are arranged in the order of time delay to form the time delay tap subsequence of the candidate cluster in the energy envelope sequence. Different candidate clusters generate independent time delay tap subsequences that do not overlap.

[0120] Read the energy values ​​and delay points corresponding to all delay taps within a single delay tap subsequence, perform overall distribution statistics on all delay points in the sequence along with their corresponding energy values, and calculate the center delay point of the overall energy concentration distribution of the delay taps. This center delay point is the delay centroid position of the candidate cluster, and each delay tap subsequence generates a unique delay centroid position.

[0121] Extract the centroid positions of the time delays of two adjacent candidate clusters, calculate the time delay difference between the two centroid positions as the inter-cluster spacing, and perform a complete comparison between the calculated inter-cluster spacing and a preset spacing threshold. The preset spacing threshold is fixed at 1 symbol period. When the inter-cluster spacing is less than 1 symbol period, it is determined that the two candidate clusters belong to the same multipath signal interval; otherwise, it is determined to be an independent multipath cluster. When the inter-cluster spacing does not exceed the preset spacing threshold, it is determined that the two candidate clusters belong to the same multipath signal interval. Merge all time delay taps contained in the two candidate clusters into the same multipath cluster. After traversing all adjacent candidate clusters to complete the comparison and merging operation, all the re-divided multipath clusters are uniformly integrated to form the multipath cluster grouping result of the energy envelope sequence.

[0122] The system reads the centroid positions and coverage ranges of all time delays corresponding to each multipath cluster as recorded in the multipath cluster grouping results. It then arranges all time delay intervals corresponding to all multipath clusters on a unified time delay coordinate axis, fully records the time delay intervals and energy distribution of each multipath cluster, and integrates and summarizes all recorded information to generate the multipath interference time delay distribution of the wireless frequency band signal. The multipath interference time delay distribution fully carries the time delay interval characteristics corresponding to all multipath interferences in the wireless channel.

[0123] The cluster delay range corresponding to each multipath cluster within the multipath interference delay distribution is read. The response intensity of the fractional interval equalization tap is adjusted according to the signal distortion degree corresponding to each cluster delay range. The effect weight of each equalization tap is redistributed to match the signal distortion characteristics of each multipath delay interval. All equalization taps with redistributed weights are arranged and integrated in sequence according to the delay order to form the recombined tap coefficient sequence of the wireless frequency band signal. Each tap coefficient within the recombined tap coefficient sequence is adapted to the multipath interference distortion characteristics of the corresponding interval.

[0124] The complete recombined tap coefficient sequence is retrieved, and the recombined tap coefficient sequence is matched with the wireless frequency band signal at each time delay point. Amplitude and phase compensation corrections are performed on the time delay component corresponding to each multipath distortion in the wireless frequency band signal. After the signal distortion components corresponding to all multipath interferences are compensated, the signal trailing distortion caused by multipath transmission in the wireless channel is eliminated. After the processing is completed, the wireless purification signal of the power dual-mode communication is output.

[0125] The beneficial effects are as follows: by extracting the energy envelope sequence of the wireless band signal, the energy delay variation law of the wireless channel multipath is completely restored; by relying on the amplitude jump along the initial cluster boundary, the multipath interval is initially divided; by combining the energy centroid within the cluster and the inter-cluster spacing, the multipath clusters are accurately merged, generating a multipath interference delay distribution that fits the real channel transmission state; and by relying on this distribution, the fractional interval equalization tap coefficients are specifically recombined to carry out equalization filtering, which can accurately compensate for the multipath signal distortion in different delay intervals, fully filter out the signal distortion caused by multipath interference in the wireless channel, retain the effective transmission signal of the wireless branch, reduce the bit error caused by the signal distortion in the wireless demodulation stage, and form a more compatible dual-mode two-path clean signal with the carrier branch purified signal, providing high-quality basic data for the subsequent two-path soft bit weighted merging.

[0126] D4. Perform carrier coherent demodulation and wireless coherent demodulation on the carrier purification signal and the wireless purification signal respectively to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence of the power dual-mode communication.

[0127] In this embodiment of the invention, the step of performing carrier coherent demodulation and wireless coherent demodulation on the carrier cleanup signal and the wireless cleanup signal, respectively, to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence for the power dual-mode communication, includes:

[0128] Carrier phase recovery is performed on the carrier cleanup signal to obtain the carrier in-phase component and carrier quadrature component of the carrier cleanup signal;

[0129] Symbol decision metric extraction is performed on the in-phase carrier component and the quadrature carrier component to obtain the carrier decision metric value of the carrier cleanup signal, and the carrier soft bit value of the carrier cleanup signal is determined based on the carrier decision metric value.

[0130] Carrier phase recovery is performed on the wireless purification signal to obtain the wireless in-phase component and the wireless quadrature component of the wireless purification signal.

[0131] Symbol decision metric extraction is performed on the wireless in-phase component and the wireless quadrature component to obtain the wireless decision metric value of the wireless decontamination signal, and the wireless soft bit value of the wireless decontamination signal is determined based on the wireless decision metric value.

[0132] The carrier soft bit value and the wireless soft bit value are time-sequentially arranged to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence for the power dual-mode communication.

[0133] The complete time-domain data of the carrier cleanup signal is read, the carrier phase information that is offset during signal transmission is extracted, the signal phase change trajectory is continuously tracked and the phase offset is compensated, and a phase-locked loop phase recovery algorithm based on pilot interpolation is adopted. Sixteen pilot symbols are uniformly inserted within the frame for phase tracking to eliminate the phase deviation caused by the channel transmission process. The signal after phase compensation is decomposed into two mutually orthogonal signal components. One is arranged along the reference phase axis to form the carrier in-phase component of the carrier cleanup signal, and the other is arranged perpendicular to the reference phase axis to form the carrier orthogonal component of the carrier cleanup signal.

[0134] The amplitude data corresponding to the in-phase component and quadrature component of the carrier are read synchronously in real time. The amplitude data of the two components are compared with the reference amplitude range corresponding to the standard communication symbols one by one. The matching degree between the current signal and various standard symbols is statistically analyzed. The statistically obtained matching degree value is uniformly used as the carrier decision metric value of the carrier purification signal. According to the matching degree between the signal and the standard symbols reflected by the carrier decision metric value, the corresponding confidence level is divided. Different confidence levels correspond to different values ​​of confidence representation quantity. This confidence representation quantity is the carrier soft bit value of the carrier purification signal. The soft bit value adopts the log-likelihood ratio (LLR) form and takes a value range of [-127, 127]. Positive numbers represent bit 1 confidence and negative numbers represent bit 0 confidence.

[0135] Read all time-domain data of the complete wireless purification signal, track the continuously offset carrier phase information during wireless channel transmission, continuously calculate the phase offset value and complete the phase compensation operation to eliminate the phase rotation deviation caused by the wireless multipath channel, and split the wireless purification signal after phase correction to generate two orthogonal signal components. One of them is distributed along the standard phase reference and is the wireless in-phase component of the wireless purification signal, and the other is distributed perpendicular to the standard phase reference and is the wireless orthogonal component of the wireless purification signal.

[0136] The amplitude data corresponding to the in-phase and quadrature components of the wireless signal are read synchronously in real time. The amplitude data of the two components are compared with the reference amplitude range corresponding to the wireless communication standard symbols one by one. The matching degree between the current received signal and each type of standard symbol is calculated. The calculated matching degree value is defined as the wireless decision metric value of the wireless purification signal. Based on the signal matching confidence reflected by the wireless decision metric value, the corresponding confidence characterization value is divided. The confidence characterization value is the wireless soft bit value of the wireless purification signal.

[0137] According to the time sequence of signal transmission, all carrier soft bit values ​​obtained by symbol-by-symbol processing are sequentially arranged end to end. The complete set of continuous data constitutes the carrier demodulation soft bit sequence of the power dual-mode communication. Synchronously, according to the unified transmission time sequence, all wireless soft bit values ​​obtained by symbol-by-symbol processing are sequentially arranged. The complete set of continuous data constitutes the wireless demodulation soft bit sequence of the power dual-mode communication.

[0138] The beneficial effects are as follows: by performing independent carrier phase recovery operations on the two purified signals, phase offset interference caused by the transmission of the two types of channels is completely eliminated; symbol decision metric values ​​are extracted based on orthogonal components to generate soft bit values ​​carrying complete confidence information; effective confidence information in the signal is completely preserved; the two soft bit values ​​are strictly regularized according to a unified timing sequence to form an ordered soft bit sequence, avoiding interference caused by timing misalignment to subsequent bit weighting and merging; the signal confidence characteristics of the carrier branch and the wireless branch are completely preserved; the data matching accuracy of the subsequent dual-mode soft bit fusion stage is improved; and the negative impact of channel phase distortion on the final bit output result is reduced.

[0139] D5. The bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence are combined using a signal-to-noise ratio weighted sum to obtain the combined soft bit value of the power dual-mode communication.

[0140] In this embodiment of the invention, the step of performing signal-to-noise ratio weighted combining of the bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence to obtain the combined soft bit value of the power dual-mode communication includes:

[0141] The carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence are aligned at the bit level to obtain the aligned carrier soft bit sequence and the aligned wireless soft bit sequence for the power dual-mode communication.

[0142] The soft bit amplitudes of the aligned carrier soft bit sequence and the aligned wireless soft bit sequence are extracted respectively to obtain the carrier soft bit amplitude and wireless soft bit amplitude of the power dual-mode communication.

[0143] The combined soft-bit value of the power dual-mode communication is calculated using the aligned carrier soft-bit sequence, the aligned radio soft-bit sequence, the carrier soft-bit amplitude, and the radio soft-bit amplitude. The formula for calculating the combined soft-bit value is as follows:

[0144] ;

[0145] in, For the merged soft bit value, The soft bit values ​​of the aligned carrier soft bit sequence. The soft bit values ​​of the aligned wireless soft bit sequence. The carrier soft bit amplitude, The amplitude of the wireless soft bit is mentioned.

[0146] The time stamp corresponding to each soft bit in the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence is read bit by bit. Using the unified signal transmission timing as the alignment reference, the arrangement position of the soft bits in the two sets of sequences is adjusted so that the carrier soft bits and the wireless soft bits representing the same transmission information are in the same position in the sequence. After completing the timing matching and correction of all the bit-specific bits, the complete bit data sets with one-to-one correspondence of positions form the aligned carrier soft bit sequence and the aligned wireless soft bit sequence of the power dual-mode communication.

[0147] The system iterates through the soft bits corresponding to each position within the aligned carrier soft bit sequence, reads the numerical fluctuation amplitude data inherent in each group of soft bits, and uniformly summarizes and defines the carrier soft bit amplitude of the power dual-mode communication. Simultaneously, it iterates through the soft bits of the same position within the aligned wireless soft bit sequence, reads the numerical fluctuation amplitude data of the corresponding soft bit, and uniformly summarizes and defines the wireless soft bit amplitude of the power dual-mode communication.

[0148] The soft bit values ​​of the aligned carrier soft bit sequence, the soft bit values ​​of the aligned wireless soft bit sequence, the carrier soft bit amplitude, and the wireless soft bit amplitude are retrieved synchronously at the same position. These four types of data are then synchronously substituted into the fusion calculation process. The information weights corresponding to the two signals are assigned based on the two soft bit amplitudes as a weighting reference. The two soft bit information after weight allocation are then fused and superimposed. After the fusion and superposition process is completed, a single integrated confidence value is generated. This integrated confidence value is the combined soft bit value of the power dual-mode communication.

[0149] The soft bit values ​​of the aligned carrier soft bit sequence are taken from the confidence representation values ​​corresponding to a single bit position within the aligned carrier soft bit sequence obtained after completing the bit-level alignment operation. The soft bit values ​​of the aligned wireless soft bit sequence are taken from the confidence representation values ​​carried by the aligned wireless soft bit sequence at the same time position. The carrier soft bit amplitude is taken from the numerical fluctuation amplitude data inherent in the corresponding soft bit within the aligned carrier soft bit sequence. The wireless soft bit amplitude is taken from the numerical fluctuation amplitude data corresponding to the soft bit at the same time position within the aligned wireless soft bit sequence. All four types of parameters are deterministic processing products output from the previous dual-mode signal demodulation, bit timing alignment, and amplitude extraction processes. The four types of parameters carry complete information of two channels corresponding to the same transmission symbol under the same timing. The four types of parameters have completely consistent timing references to ensure that the dimensions match and are consistent with each other.

[0150] A weighted fusion operation is performed based on the soft-bit confidence values ​​and corresponding amplitude data after two time-aligned channels. Throughout the operation, the current transmission reliability of the corresponding channel is represented by the amplitude of a single soft-bit. The soft-bit value of one channel is combined with its own amplitude and the amplitude of the other channel to complete the weighting term. The two sets of weighting terms, corresponding to the carrier branch and the wireless branch respectively, are summed in the numerator. The soft-bit confidence values ​​of the two sets of weighting terms are removed, and only the amplitude-related components are retained to complete the summing in the denominator. The summed numerator and the summed denominator are compared to generate the merged soft-bit value. This fully realizes the adaptive weighted fusion of confidence information of the wave communication branch and the wireless communication branch under the same transmission symbol. The weighting ratio of the branch with higher amplitude value is increased synchronously, and the weighting ratio of the branch with lower amplitude value is decreased synchronously. This balances and integrates the effective transmission information carried by the two channels and suppresses the confidence bias caused by single-channel noise.

[0151] When the amplitude of a single soft bit continuously increases, the proportion of the corresponding weighted term in the summation results of the numerator and denominator of that branch continuously increases synchronously. The merged soft bit value will continuously approach the soft bit confidence value of that branch. When the amplitude of a single soft bit continuously decreases, the proportion of the corresponding weighted term in the summation results of the numerator and denominator of that branch continuously decreases synchronously. The merged soft bit value will continuously deviate from the soft bit confidence value of that branch and approach the soft bit confidence value of another branch with a higher amplitude. When the amplitudes of the two soft bits maintain the same change range and increase or decrease synchronously, the proportion of the weighted terms of the two channels remains constant. The merged soft bit value stably maintains the fixed weighted median value of the soft bit confidence values ​​of the two channels. The fusion weights of the two channels are dynamically adjusted by the change in amplitude throughout the process. The change range of the weights and the change range of the amplitude form a synchronous linear change relationship. The dimensions are synchronously and uniformly adapted with the amplitude and soft bit values, and there will be no dimensional imbalance problem.

[0152] The beneficial effects are that bit-level timing alignment operation eliminates the timing misalignment problem of the two demodulation sequences, ensures that the two soft bits corresponding to the same transmitted information participate in the weighted operation synchronously, and allocates corresponding fusion weights based on the channel signal-to-noise ratio characteristics carried by the amplitude of the two soft bits, so as to realize the adaptive fusion of the carrier and wireless communication information, give full play to the transmission quality advantages of the two channels, amplify the reference role of the soft bit information of the high signal-to-noise ratio branch, weaken the distortion information carried by the low signal-to-noise ratio branch, make the merged soft bit value have higher information confidence, and reduce the interference of single channel noise defects on the final bit information.

[0153] D6. Perform polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication.

[0154] In this embodiment of the invention, the step of performing polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication includes:

[0155] A time-series sliding truncation is performed on the merged soft bit value to obtain a local data window of the merged soft bit value;

[0156] The dynamic decision boundary for the merged soft bit value is obtained based on the degree of data dispersion within the local data window.

[0157] Based on the dynamic decision boundary, the sign attribute of the merged soft bit value is determined to obtain the preliminary logical sequence of the merged soft bit value;

[0158] The preliminary logic sequence is logically smoothed to obtain the anti-interference output bit stream of the power dual-mode communication.

[0159] The merged soft bit values ​​of multiple adjacent positions are retrieved sequentially according to the time sequence. A fixed number of continuously arranged merged soft bit values ​​are selected to form an independent data interval. The start and end positions of the selected interval are continuously moved backward in a fixed step. Each interval selection operation generates a set of independent interval data. Each set of interval data is a local data window of the merged soft bit values.

[0160] Read all merged soft bit values ​​within a single local data window to perform global numerical distribution statistics. Analyze the degree of dispersion among all values ​​within the window and quantify the dispersion using the standard deviation of the data within the window. The larger the standard deviation, the stronger the current local noise interference. Combine the overall distribution of the current window values ​​to define a numerical boundary standard that adapts to the current noise level. This numerical boundary standard that adapts to the real-time data distribution is the dynamic decision boundary of the merged soft bit values.

[0161] The specific value of a single merged soft bit value is compared with the dynamic decision boundary generated by the corresponding local data window. Based on the different intervals on both sides of the dynamic decision boundary, corresponding logical identifiers are divided. The logical identifiers generated by matching each merged soft bit value are arranged in the original time sequence. All logical identifiers are combined to form the preliminary logical sequence of the merged soft bit value.

[0162] The logic identifiers of the initial logic sequence are read segment by segment along the time sequence. A sudden logical point is identified in the sequence that is inconsistent with the adjacent identifiers before and after it. The correction process is completed by a three-bit sliding median smoothing algorithm to eliminate irregular and scattered sudden logical points in the sequence. The ordered and coherent continuous logic data set after the complete correction process is the anti-interference output bit stream of the power dual-mode communication.

[0163] The beneficial effects are that the time-series sliding truncation to generate local data windows can capture the distribution characteristics of merged soft bit values ​​in local intervals in real time. The dynamic decision boundary generated by the discreteness of the window data can adapt to the real-time changing channel noise environment, avoid the discrimination bias caused by fixed decision boundaries, and eliminate isolated abrupt logical points in the sequence through logical smoothing, further suppressing bit transition errors caused by noise. The final anti-interference output bit stream has a lower bit error rate, and fully guarantees the accuracy and continuity of data transmission in power dual-mode communication under complex interference scenarios.

[0164] like Figure 2 The diagram shown is a functional block diagram of a power dual-mode communication anti-interference system based on filter optimization provided in an embodiment of the present invention.

[0165] The power line dual-mode communication anti-interference system 100 based on filter optimization described in this invention can be installed in electronic devices. Depending on the functions implemented, the power line dual-mode communication anti-interference system 100 may include a frequency band separation module 101, a carrier filtering module 102, a wireless equalization module 103, a coherent demodulation module 104, a soft bit weighting module 105, and a bit decision module 106. The modules described in this invention can also be referred to as units, which are a series of computer program segments that can be executed by the processor of an electronic device and can perform a fixed function, and are stored in the memory of the electronic device.

[0166] In this embodiment, the functions of each module / unit are as follows:

[0167] The frequency band separation module 101 is used to perform frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the wireless frequency band signal of the power dual-mode communication.

[0168] The carrier filtering module 102 is used to perform multi-level notch filtering optimization on the carrier frequency band signal according to the interference frequency point distribution characteristics of the carrier frequency band signal, so as to obtain the carrier purified signal of the power dual-mode communication.

[0169] The wireless equalization module 103 is used to perform multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and to perform fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal of the power dual-mode communication.

[0170] The coherent demodulation module 104 is used to perform carrier coherent demodulation and wireless coherent demodulation on the carrier cleanup signal and the wireless cleanup signal respectively to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence of the power dual-mode communication.

[0171] The soft bit weighting module 105 is used to perform signal-to-noise ratio weighted merging of the bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence to obtain the merged soft bit value of the power dual-mode communication.

[0172] The bit decision module 106 is used to perform polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication.

[0173] In the several embodiments provided by this invention, it should be understood that the disclosed methods and systems can be implemented in other ways. For example, the system embodiments described above are merely illustrative; for instance, the division of modules is only a logical functional division, and other division methods may be used in actual implementation.

[0174] The modules described as separate components may or may not be physically separate. The components shown as modules may or may not be physical units; that is, they may be located in one place or distributed across multiple network units. Some or all of the modules can be selected to achieve the purpose of this embodiment according to actual needs.

[0175] Furthermore, the functional modules in the various embodiments of the present invention can be integrated into one processing unit, or each unit can exist physically separately, or two or more units can be integrated into one unit. The integrated unit can be implemented in hardware or in the form of hardware plus software functional modules.

[0176] It will be apparent to those skilled in the art that the present invention is not limited to the details of the exemplary embodiments described above, and that the present invention can be implemented in other specific forms without departing from the spirit or essential characteristics of the present invention.

[0177] This application embodiment can acquire and process relevant data based on artificial intelligence technology. Artificial intelligence is the theory, method, technology, and application system that uses digital computers or machines controlled by digital computers to simulate, extend, and expand human intelligence, perceive the environment, acquire knowledge, and use that knowledge to obtain optimal results.

[0178] Finally, it should be noted that the above embodiments are only used to illustrate the technical solutions of the present invention and are not intended to limit it. Although the present invention has been described in detail with reference to preferred embodiments, those skilled in the art should understand that modifications or equivalent substitutions can be made to the technical solutions of the present invention without departing from the spirit and scope of the technical solutions of the present invention.

Claims

1. A power line dual-mode communication anti-interference method based on filter optimization, characterized in that, The method includes: D1. Perform frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the wireless frequency band signal of the power dual-mode communication; D2. Based on the interference frequency distribution characteristics of the carrier frequency band signal, perform multi-level notch filtering optimization on the carrier frequency band signal to obtain the carrier purified signal for the power dual-mode communication; D3. Perform multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and perform fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal of the power dual-mode communication. D4. Perform carrier coherent demodulation and wireless coherent demodulation on the carrier purification signal and the wireless purification signal respectively to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence of the power dual-mode communication. D5. The bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence are combined using a signal-to-noise ratio weighted sum to obtain the combined soft bit value of the power dual-mode communication. D6. Perform polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication.

2. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 1, characterized in that, The process of performing frequency band separation processing on the digital hybrid signal of the power dual-mode communication to obtain the carrier frequency band signal and the radio frequency band signal of the power dual-mode communication includes: The digital hybrid signal of the power dual-mode communication is acquired, and the digital hybrid signal is windowed and framed in the time domain to obtain the frame sequence of the digital hybrid signal; Based on the frame sequence, frequency analysis and conversion are performed on the digital mixed signal to obtain the frequency domain complex spectrum sequence of the digital mixed signal; Based on the spectral line energy distribution in the frequency domain complex spectrum sequence, extract the carrier band energy centroid and the wireless band energy centroid of the digital mixed signal; Based on the energy centroid of the carrier frequency band and the energy centroid of the wireless frequency band, carrier passband mask extraction and wireless passband mask extraction are performed on the frequency domain complex spectrum sequence to obtain the carrier frequency band signal and wireless frequency band signal of the power dual-mode communication.

3. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 1, characterized in that, The step of performing multi-level notch filtering optimization on the carrier frequency band signal based on the interference frequency distribution characteristics of the carrier frequency band signal to obtain the carrier cleaned signal for the power dual-mode communication includes: A sliding window spectral energy accumulation process is performed on the carrier frequency band signal to obtain the spectral energy accumulation sequence of the carrier frequency band signal; Based on the local extreme value distribution of the accumulated spectral energy sequence, determine the peak position of the accumulated spectral energy and the frequency width of the accumulated spectral energy sequence. The peak position of the spectral energy is taken as the interference frequency point position of the carrier frequency band signal, and the frequency width of the spectral energy is taken as the interference frequency point bandwidth of the carrier frequency band signal. Based on the location and bandwidth of the interference frequency point, the stopband configuration parameters of the carrier frequency band signal are generated; Based on the stopband configuration parameters, the carrier frequency band signal is subjected to step-by-step notch filtering to obtain the carrier cleaned signal for the power dual-mode communication.

4. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 3, characterized in that, The step of performing step-by-step notch filtering on the carrier frequency band signal based on the stopband configuration parameters to obtain the carrier cleaned signal for the power dual-mode communication includes: Based on the stopband configuration parameters, amplitude suppression is performed on the frequency domain spectral lines corresponding to the interference frequency points in the carrier frequency band signal to obtain the first-level clean signal of the carrier frequency band signal; Amplitude suppression is performed on the frequency domain spectral line at the next interference frequency point in the first-level purified signal to obtain the second-level purified signal of the carrier frequency band signal; The operation of amplitude suppression of the frequency domain spectral line at the next interference frequency point in the current level of the clean signal is repeated until amplitude suppression is completed for the frequency domain spectral lines at all interference frequency points in the carrier frequency band signal, and the last level of clean signal is used as the carrier clean signal for the power dual-mode communication.

5. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 1, characterized in that, The process of estimating the multipath delay of the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and performing fractional-interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal for the power dual-mode communication, includes: Energy envelope extraction is performed on the wireless frequency band signal to obtain the energy envelope sequence of the wireless frequency band signal; Initial cluster boundary labeling is performed on the amplitude transition edges in the energy envelope sequence to obtain the initial cluster boundary label of the energy envelope sequence; Based on the initial cluster boundary markers, the time delay taps in the energy envelope sequence are grouped and merged to obtain the multipath cluster grouping results of the wireless band signal; Based on the multipath cluster grouping results, the multipath interference delay distribution of the wireless frequency band signal is generated; Based on the cluster delay range in the multipath interference delay distribution, the fractional interval equalization tap coefficients of the wireless band signal are reconfigured to obtain the reconfigured tap coefficient sequence of the wireless band signal. Based on the recombined tap coefficient sequence, the wireless frequency band signal is subjected to fractional interval equalization filtering to obtain the wireless purification signal for the power dual-mode communication.

6. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 5, characterized in that, The step of grouping and merging the time delay taps in the energy envelope sequence based on the initial cluster boundary markers to obtain the multipath cluster grouping results of the wireless frequency band signal includes: Based on the initial cluster boundary markers, determine the positions of the candidate cluster heads and tails in the energy envelope sequence; Based on the candidate cluster head position and the candidate cluster tail position, extract the time delay tap subsequence of the candidate cluster in the energy envelope sequence; The intra-cluster energy centroid is estimated for the time delay tap subsequence to obtain the time delay centroid position of the candidate cluster; Based on the time delay centroid position of the candidate cluster, the inter-cluster spacing of adjacent candidate clusters is determined, and adjacent candidate clusters with an inter-cluster spacing less than a preset spacing threshold are merged into the same multipath cluster to obtain the multipath cluster grouping result of the wireless frequency band signal.

7. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 1, characterized in that, The step of performing carrier coherent demodulation and wireless coherent demodulation on the carrier cleanup signal and the wireless cleanup signal, respectively, to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence for the power dual-mode communication includes: Carrier phase recovery is performed on the carrier cleanup signal to obtain the carrier in-phase component and carrier quadrature component of the carrier cleanup signal; Symbol decision metric extraction is performed on the in-phase carrier component and the quadrature carrier component to obtain the carrier decision metric value of the carrier cleanup signal, and the carrier soft bit value of the carrier cleanup signal is determined based on the carrier decision metric value. Carrier phase recovery is performed on the wireless purification signal to obtain the wireless in-phase component and the wireless quadrature component of the wireless purification signal. Symbol decision metric extraction is performed on the wireless in-phase component and the wireless quadrature component to obtain the wireless decision metric value of the wireless decontamination signal, and the wireless soft bit value of the wireless decontamination signal is determined based on the wireless decision metric value. The carrier soft bit value and the wireless soft bit value are time-sequentially arranged to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence for the power dual-mode communication.

8. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 1, characterized in that, The step of performing signal-to-noise ratio weighted combining of the bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence to obtain the combined soft bit value for the power dual-mode communication includes: The carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence are aligned at the bit level to obtain the aligned carrier soft bit sequence and the aligned wireless soft bit sequence for the power dual-mode communication. The soft bit amplitudes of the aligned carrier soft bit sequence and the aligned wireless soft bit sequence are extracted respectively to obtain the carrier soft bit amplitude and wireless soft bit amplitude of the power dual-mode communication. The combined soft-bit value of the power dual-mode communication is calculated using the aligned carrier soft-bit sequence, the aligned radio soft-bit sequence, the carrier soft-bit amplitude, and the radio soft-bit amplitude. The formula for calculating the combined soft-bit value is as follows: ； in, For the merged soft bit value, The soft bit values ​​of the aligned carrier soft bit sequence. The soft bit values ​​of the aligned wireless soft bit sequence. The carrier soft bit amplitude, The amplitude of the wireless soft bit is mentioned.

9. The anti-interference method for power dual-mode communication based on filter optimization as described in claim 1, characterized in that, The step of performing polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication includes: A time-series sliding truncation is performed on the merged soft bit value to obtain a local data window of the merged soft bit value; The dynamic decision boundary for the merged soft bit value is obtained based on the degree of data dispersion within the local data window. Based on the dynamic decision boundary, the sign attribute of the merged soft bit value is determined to obtain the preliminary logical sequence of the merged soft bit value; The preliminary logic sequence is logically smoothed to obtain the anti-interference output bit stream of the power dual-mode communication.

10. A power line dual-mode communication anti-interference system based on filter optimization, characterized in that, The system is used to implement the power dual-mode communication anti-interference method based on filter optimization as described in claim 1, the system comprising: The frequency band separation module is used to perform frequency band separation processing on the digital mixed signal of the power dual-mode communication to obtain the carrier frequency band signal and the wireless frequency band signal of the power dual-mode communication; The carrier filtering module is used to perform multi-level notch filtering optimization on the carrier frequency band signal according to the interference frequency point distribution characteristics of the carrier frequency band signal to obtain the carrier cleaned signal of the power dual-mode communication. A wireless equalization module is used to perform multipath delay estimation on the wireless frequency band signal to obtain the multipath interference delay distribution of the wireless frequency band signal, and to perform fractional interval equalization on the wireless frequency band signal based on the multipath interference delay distribution to obtain the wireless purification signal of the power dual-mode communication. The coherent demodulation module is used to perform carrier coherent demodulation and wireless coherent demodulation on the carrier cleanup signal and the wireless cleanup signal respectively to obtain the carrier demodulation soft bit sequence and the wireless demodulation soft bit sequence of the power dual-mode communication. A soft bit weighting module is used to perform signal-to-noise ratio weighted merging of the bit values ​​of the carrier demodulation soft bit sequence and the bit values ​​of the wireless demodulation soft bit sequence to obtain the merged soft bit value of the power dual-mode communication. The bit decision module is used to perform polarity discrimination mapping on the merged soft bit values ​​to obtain the anti-interference output bit stream of the power dual-mode communication.

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