Wireless networking LED constant current charging and discharging management system

Abstract

The application is particularly a wireless networking LED constant current charging and discharging management system, and relates to the technical field of LED lighting control, comprising: a photoelectric multiplexing and state isolation module; a micro-energy pumping and collecting module; a transient energy accumulation and gating module; a minimalist sniffing communication module; and an MS hardware strong enable and bypass reset module.In the application, the photoelectric multiplexing and state isolation design of the pure semiconductor structure can realize automatic and seamless switching of the lighting driving loop and the energy collecting loop without additional power supply, high reliability electrical isolation is realized by using the inherent physical characteristics of semiconductor devices, and the consumption of weak light-generated energy by the parasitic parameters of the driving loop is avoided.The existing LED light-emitting array is only reused to realize the environmental light energy recovery without additional photovoltaic collector, and the system hardware cost is effectively controlled.

Description

Technical Field

[0001] This invention relates to the field of LED lighting control technology, and in particular to a wireless network LED constant current charging and discharging management system. Background Technology

[0002] With the deep integration of the Internet of Things (IoT) and smart lighting technology, LED lighting systems based on wireless networking architecture have been widely applied in large-scale scenarios such as urban roads, park landscapes, tunnel emergency lighting, and outdoor lighting in remote areas. In the existing technological system, mature technical solutions have been developed for LED constant current driving, multi-node wireless networking communication, and lithium battery charging and discharging management. These solutions enable precise constant current control of LED lighting, clustered remote regulation, and safe charging and discharging protection of batteries, providing a stable operating foundation for large-scale deployment of smart lighting systems and promoting their application in various complex scenarios.

[0003] Utilizing the photovoltaic characteristics of the PN junction of LED light-emitting arrays to collect and reuse ambient light energy has become an important research direction that balances system hardware costs and passive power-saving capabilities. At the same time, how to achieve compatibility and adaptation between the lighting drive circuit and the energy harvesting circuit without changing the main lighting architecture of the system, and ensure stable operation in both working modes, has also become an important technical research direction in this field.

[0004] To address the challenges of collecting nanowatt- to microwatt-level ambient light energy from LED arrays and the need for system wake-up after battery undervoltage protection, the industry is continuously exploring adaptation solutions for low-power energy management and remote wake-up technologies. Key technological challenges include: achieving efficient energy pumping and positive accumulation under extremely low light input conditions; reliably identifying wireless wake-up signals within a very short time window supported by minimal energy; and reliably waking up the battery management system from undervoltage lockup states using low-power triggering logic. These challenges represent crucial technological breakthroughs for improving the maintenance-free operation capabilities of intelligent lighting systems.

[0005] Therefore, a wireless network LED constant current charging and discharging management system is proposed to address the aforementioned problems. Summary of the Invention

[0006] The purpose of this invention is to provide a wireless network LED constant current charging and discharging management system to solve the above-mentioned problems.

[0007] To achieve the above objectives, the present invention adopts the following technical solution: A wireless network LED constant current charging and discharging management system includes: The optoelectronic multiplexing and state isolation module is configured to disconnect the LED light-emitting array from the main constant current drive controller and physically isolate the LED light-emitting array and switch it to the micro energy pump and collection module when the main battery is cut off due to undervoltage lockout triggered by power failure. The micro-energy pump and harvesting module is configured to receive the LED light-emitting array connected via the optoelectronic multiplexing and state isolation module, collect the reverse photogenerated voltage generated by the array under ambient light, and inject electrical energy into the transient energy storage and gating module after dynamic impedance matching and static current boosting. The transient energy storage and gating module is configured to store electrical energy from the micro-energy pump and collection module and monitor the voltage of the energy storage medium. When the voltage exceeds the set upper limit threshold, it instantly opens the gate to provide a controlled burst transient power supply window to the simplified sniffing communication module. The minimalist sniffing communication module is configured to instantly start using the transient energy storage and the transient power supply window provided by the gating module. It acquires external wake-up commands in the space within a preset time before the energy is exhausted, and outputs and latches a state holding signal to the BMS hardware forced start and bypass reset module before power failure. The MS hardware forced start and bypass reset module is configured to be triggered by the status hold signal transmitted from the simplified sniffing communication module. It utilizes the voltage relaxation effect of the main battery to conduct the controlled bypass, guides the advance current to trigger the main control MCU to power on and boot, and then the main control MCU takes over and forcibly releases the undervoltage lockout of the battery management system to restore power to the entire system.

[0008] Preferably, the optoelectronic multiplexing and state isolation module includes a main cut-off tube M1 and an energy harvesting bypass tube M2; The anode of the LED light-emitting array is connected to the positive output terminal of the constant current drive controller, and its cathode is connected to node A; The main disconnect pipe M1 is connected between node A and the power ground loop, and the energy harvesting bypass pipe M2 is connected between node A and the input node B of the micro energy pump and harvesting module. The gates of the main cut-off tube M1 and the energy harvesting bypass tube M2 receive status indication signals converted by the system power rail voltage.

[0009] Preferably, the main cut-off transistor M1 is a P-channel enhancement-mode MOSFET, and the energy harvesting bypass transistor M2 is a depletion-mode N-channel MOSFET or a low-turn-threshold enhancement-mode N-MOS. When in the deep sleep isolation state, the status indicator signal drops to 0V, the main cut-off transistor M1 is turned off and its parasitic diode is directed from the drain to the source to reverse the leakage current, the energy harvesting bypass transistor M2 is turned on, and the LED light-emitting array is physically connected to node B.

[0010] Preferably, the micro-energy pump and harvest module uses a pure hardware fractional open-circuit voltage method for hardware maximum power point tracking; The micro-energy pump and harvest module includes a nanowatt-level low-frequency oscillator, a sample-and-hold capacitor, and a high-resistance voltage divider network. The nanowatt-level low-frequency oscillator periodically disconnects its input terminal to measure the absolute open-circuit voltage of the LED array. After being divided by a fixed ratio, the voltage is stored in the sample-and-hold capacitor as a reference voltage, which is used to dynamically adjust the equivalent input impedance.

[0011] Preferably, the micro-energy pump and harvest module further includes an inductor boost topology or an asynchronous charge pump with extremely low quiescent current; The inductor boost topology is controlled by a hysteresis controller. When the input voltage exceeds the reference voltage, it outputs a very short conduction pulse to drive the input switch. The energy is then pumped to the transient energy storage and gating module through a miniature power inductor and a Schottky rectifier diode.

[0012] Preferably, the transient energy storage and gating module includes: Energy storage medium composed of multilayer ceramic capacitor arrays or micro supercapacitors, and deep subthreshold hysteresis comparators; The deep subthreshold hysteresis comparator has its internal field-effect transistor biased in the deep subthreshold region. When it detects that the voltage of the energy storage medium slowly crosses the set upper limit turn-on threshold, it flips to output a high level. When the voltage drops to the lower limit turn-off threshold, it flips to output a low level.

[0013] Preferably, the transient energy storage and gating module further includes a load switch with an internally integrated Miller capacitor soft-start circuit; The load switch is controlled by the output level of the deep subthreshold hysteresis comparator. The Miller effect is used to limit the surge current generated when power is supplied to the simplified sniffing communication module, preventing the voltage of the energy storage medium from dropping below the lower limit turn-off threshold momentarily.

[0014] Preferably, the simplified sniffing communication module adopts a pure hardware bare-metal boot timing sequence. After power-on, it bypasses the boot loading program, starts oscillating quickly through the internal low-speed RC oscillator, and directly overwrites the radio frequency physical layer registers, forcing the receiver front-end to enter pure receiving mode. The wake-up command is captured by performing sliding cross-correlation calculation on the physical layer preamble in space using an internal hardware correlator, without any MAC layer software intervention.

[0015] Preferably, after the hardware correlator detects a relevant peak value, the simplified sniffing communication module triggers an internal interrupt and pulls the state holding pin belonging to the normally open power domain high. The status holding pin is connected to an external parasitic bypass capacitor. Even after the transient power supply window ends and the main body of the communication module loses power, it can still maintain a high-level status holding signal for a preset duration to the BMS hardware forced start and bypass reset module.

[0016] Preferably, the BMS hardware forced start and bypass reset module adopts a two-stage cascaded trigger architecture, including a primary trigger and a current-limiting resistor; After receiving the state hold signal, the primary trigger turns on and leads the relaxation voltage of the main battery to the system bus through the current limiting resistor; After the system bus voltage is boosted, the main control MCU is triggered to power on and take over. The main control MCU outputs a lockout command to maintain bypass conduction and completes the BMS software handshake through the bus to forcibly release the undervoltage lockout state.

[0017] In summary, due to the adoption of the above technical solution, the beneficial effects of the present invention are: 1. This invention utilizes a pure semiconductor architecture for optoelectronic multiplexing and state isolation, enabling automatic and seamless switching between the lighting drive circuit and the energy harvesting circuit without the need for an additional power supply. It leverages the inherent physical characteristics of semiconductor devices to achieve highly reliable electrical isolation, avoiding the consumption of weak photogenerated energy by parasitic parameters in the drive circuit. No additional photovoltaic harvesting devices are required; ambient light energy recovery can be achieved simply by reusing the existing LED array, effectively controlling system hardware costs.

[0018] 2. This invention achieves extremely low power consumption control across the entire chain through low-power impedance matching in pure hardware and intermittent energy pumping topology. It can achieve positive accumulation of weak energy in low light environment, significantly improve the efficiency of micro-energy collection, and provide a stable and reliable energy foundation for the passive power-on of the system. Attached Figure Description

[0019] Further details, features, and advantages of this application are disclosed in the following description of exemplary embodiments in conjunction with the accompanying drawings, in which: Figure 1 This is a system structure diagram of the present invention. Detailed Implementation

[0020] Several embodiments of this application will now be described in more detail with reference to the accompanying drawings to enable those skilled in the art to implement this application. This application may be embodied in many different forms and for various purposes and should not be limited to the embodiments set forth herein. These embodiments are provided to make this application thorough and complete, and to fully convey the scope of this application to those skilled in the art. The embodiments described do not limit this application.

[0021] Unless otherwise defined, all terms used herein (including technical and scientific terms) shall have the same meaning as commonly understood by one of ordinary skill in the art to which this application pertains. It will be further understood that terms such as those defined in commonly used dictionaries shall be interpreted as having a meaning consistent with their meaning in the relevant field and / or the context of this specification, and shall not be interpreted in an idealized or overly formal sense unless expressly defined herein.

[0022] Example 1 Its specific implementation method is combined with the appendix Figure 1 A detailed explanation will be provided.

[0023] Appendix Figure 1 This invention provides a structural block diagram of a wireless network LED constant current charging and discharging management system, which shows the connection relationship between the optoelectronic multiplexing and state isolation module and the MS hardware forced start and bypass reset module, and marks the main functional interaction flow of each module.

[0024] In this embodiment, it includes: Module 1: Photoelectric multiplexing and state isolation module, configured to automatically disconnect the LED light-emitting array from the main trunk constant current drive controller when the main battery is cut off due to undervoltage lockout triggered by power failure, and physically isolate the LED light-emitting array and seamlessly switch it to the micro energy pump and collection module; The key point of this module is to solve the problem of physical hard isolation between the "high-power high-voltage constant current drive circuit" and the "nanowatt-level weak energy harvesting network". If the isolation design has even a leakage current of the nanoampere (nA) level, the weak electrical energy excited by ambient light will be completely absorbed by the huge output capacitance of the preceding constant current driver. This module achieves automatic disconnection and multiplexing in the passive state through specific semiconductor switching timing and depletion layer physical characteristics.

[0025] Physical selection and network topology of core semiconductor switches: To achieve seamless state isolation, this network abandons power-consuming mechanical relays or conventional optocouplers, and is built entirely based on ultra-low leakage current field-effect transistors (MOSFETs). We define the entire LED light-emitting array as a two-port network, with an anode port and a cathode port.

[0026] In the main circuit, the anode of the LED array is directly connected to the positive output terminal of the preceding buck / boost constant current drive controller via copper traces. The core isolation logic is deployed on the cathode side. We set up a physical common node at the cathode port of the LED array, named Node A.

[0027] Main cut-off transistor (M1): A P-channel enhancement-mode MOSFET (P-MOS). Its source is connected to node A, and its drain is connected to the current sampling resistor terminal of the constant current drive controller (i.e., the power ground loop).

[0028] Energy harvesting bypass transistor (M2): It adopts an N-channel depletion-type MOSFET or a special enhancement-type N-MOS with an extremely low turn-on threshold. Its drain is connected to node A, and its source is directly connected to the input terminal of the next stage micro-energy harvesting module, which we define as node B.

[0029] Mitigation of parasitic effects in body diodes: Under extremely weak photogenerated voltage, the parasitic body diode of a MOSFET is the biggest culprit for leakage current. For M1 (P-MOS), the physical manufacturing process dictates that the body diode is oriented from the drain to the source. When the system is in a zero-power standby state powered by a battery, the LED array generates a reverse photogenerated voltage under ambient light (i.e., the potential at node A is slightly higher than the anode potential).

[0030] At this point, the body diode of M1 is in a strictly reverse biased state, which physically prevents current from flowing back from node A to the constant current driver, limiting the leakage current to the picoampere (pA) level. Similarly, the body diode of M2 must be oriented from the source to the drain to prevent the input capacitor charge of the micro-energy harvesting module from flowing back into the LED array.

[0031] Physical timing of zero-power state transition: The switching commands for the isolation modules rely entirely on the actual physical voltage of the system's main bus, rather than any software commands from the microcontroller, thus ensuring true "zero-power standby." The system extracts the system power rail voltage from the main battery management system (BMS), passes it through a high-impedance voltage divider network, and generates status indication signals, which are then connected to the gates of M1 and M2, respectively.

[0032] In normal constant current illumination mode: when the battery is healthy and the BMS outputs a normal system voltage, this high-level signal is applied to the gates of M1 and M2. For M1 (P-MOS), since the gate is pulled high and its source voltage (node ​​A, the voltage after the LED's forward voltage drop) is lower than the gate voltage, M1 conducts, connecting the LED cathode to power ground and forming a complete light-emitting circuit. For M2, if a depletion-mode transistor is used, the high-level gate will pinch-off its channel; if an enhancement-mode transistor is used, its gate will be turned off by a logic inverting circuit. At this time, the main light-emitting circuit is completely disconnected from the micro-energy harvesting network.

[0033] Deep sleep isolation state under power supply: When the battery voltage drops below the low-voltage cutoff threshold of the BMS (e.g., lithium battery drops below 2.5V), the main bus is instantly de-energized, and the status indicator signal drops to 0V. At this time, all external drives disappear. M1's gate is 0V, losing its gate-source negative bias, and it quickly turns off the main circuit by relying on its own carrier recombination. Meanwhile, when the depletion-mode M2's gate is 0V, its internal conductive channel naturally exists (determined by physical doping), and it is in a normally open conducting state. At this point, the LED light-emitting array is completely "physically removed" from the constant current drive network, and its cathode is seamlessly connected to the subsequent node B through the already conducting M2.

[0034] Module 2: Micro-energy pumping and harvesting module, configured to receive the LED light-emitting array connected via the optoelectronic multiplexing and state isolation module, collect the weak reverse photogenerated voltage generated by the array under ambient light, and after dynamic impedance matching and extremely low static current boost, continuously pump the electrical energy into the transient energy storage and gating module.

[0035] The current flowing in from node B is an extremely weak direct current generated by the separation of photogenerated electron-hole pairs in the PN junction of the light-emitting diode under the influence of the built-in electric field. The core technology of this module lies in how to overcome the forward voltage drop of silicon-based diodes under extremely harsh conditions where the input power is only tens of nanowatts (nW) to a few microwatts (μW), efficiently pump energy to a usable logic voltage level, and at the same time achieve extremely low power impedance matching.

[0036] Hardware-level maximum power point tracking (fractional open-circuit voltage method): As a non-standard photovoltaic device, LEDs exhibit drastic, non-linear fluctuations in internal resistance with varying light intensity. If the pump boost circuit is directly connected to node B, the initial surge current drawn by the boost chip will instantly pull the weak photogenerated voltage down to zero, causing the collection system to immediately shut down. Therefore, an impedance matching mechanism, namely maximum power point tracking (MPPT), must be introduced.

[0037] Given that the system cannot withstand the power consumption of any ADC sampling or digital computation, this solution employs a purely hardware-based fractional open-circuit voltage method. This method is based on empirical formulas in semiconductor physics: ; in, The voltage at the maximum power point. This is the absolute open-circuit voltage. It is a constant determined by the bandgap of the LED material (usually around 0.75).

[0038] In the circuit implementation, an ultra-low frequency nanowatt-level oscillator with a current consumption of less than 50nA (such as a CMOS NOT-gate ring oscillator operating in the subthreshold region) is introduced to generate sampling pulses with extremely long periods (e.g., once every 16 seconds) and extremely narrow pulse widths (e.g., 10 milliseconds). When the pulse arrives, the hardware logic briefly disconnects node B from the subsequent main boost circuit. At this time, the LED is in a pure open-circuit state, and the voltage at node B rapidly rises to the absolute open-circuit voltage under ambient light. This voltage is divided by a voltage divider network consisting of two high-precision thin-film resistors with a total resistance in the gigaohm range, according to... The voltage is divided proportionally. The resulting target reference voltage is injected and stored in a low-leakage sample-and-hold ceramic capacitor.

[0039] After the pulse ends, node B is reconnected to the main boost circuit. The subsequent boost controller compares the real-time input voltage with the reference voltage in the sample-and-hold capacitor, dynamically adjusting the input equivalent impedance to ensure that the LED always operates near its maximum power point.

[0040] Hysteresis cold start and pump topology with extremely low quiescent current: Since the input voltage can be as low as 1.5V or even lower as generated by a single LED, the quiescent power consumption of the error amplifier and reference source inside a conventional PWM boost controller is too high. This module uses an asynchronous charge pump or a light-load burst-mode inductor boost topology with extremely low quiescent current.

[0041] Taking burst-mode inductor boost as an example: the circuit mainly consists of an input switch with a low turn-on threshold, a miniature power inductor (L), and a Schottky rectifier diode with a low forward voltage drop. The system does not contain a continuously operating clock.

[0042] Its operating timing is entirely driven by a voltage hysteresis comparator: When the input capacitor of node B collects photogenerated charge, the voltage slowly rises and exceeds the aforementioned value. When the set value is reached, the hysteresis comparator flips, outputting a single, extremely short conduction pulse to drive the input switch. During the switch's conduction period, a weak current flows through the inductor to store energy. After the pulse ends, the switch turns off, and the inductor's freewheeling current generates a flyback high voltage, which flips the Schottky diode, pumping this tiny energy packet into the high-voltage energy storage tank of the subsequent stage.

[0043] This process is not a continuous high-frequency switching. When the ambient light is strong, the "pumping" action becomes more frequent; when the ambient light is extremely weak, a pumping operation may only occur once every few seconds. During the long interval between two pumping actions, all unnecessary bias circuits inside the controller are powered off and enter deep sleep, thereby keeping the overall average static current consumption of the module firmly suppressed to within a few hundred nanoamps, ensuring that even the weakest scattered light energy can be positively accumulated rather than dissipated by the chip's own static current.

[0044] These two modules address the most critical spatiotemporal energy conversion problem in the system: how to convert the microwatt-level energy collected during long days, which is so weak that it can hardly be detected by standard instruments, into a burst pulse that can drive the radio frequency chip to generate milliwatt-level peak power consumption in an instant, and complete complex electromagnetic wave decoding within this extremely short physical window.

[0045] Module 3: Transient Energy Storage and Gating Module, configured to store weak electrical energy from the micro-energy pump and collection module, and closely monitor the voltage of the energy storage medium through the underlying hysteresis monitoring mechanism. When the voltage slowly crosses the set upper limit threshold, the gate is opened instantly to provide a controlled burst transient power supply window to the simplified sniffing communication module.

[0046] In ultra-low power design, the biggest technical obstacle is not how to collect energy, but how to prevent the collected energy from being wasted by the leakage current of the energy storage device itself, and how to prevent the instantaneous surge current from crashing the system when the gate is opened.

[0047] Equivalent parallel impedance (EPR) and physical leakage boundary of energy storage medium: The system must never use ordinary electrolytic capacitors or inferior supercapacitors. All capacitors in the physical model contain an equivalent series resistance (ESR) and an equivalent parallel resistance (EPR). In nanowatt-scale energy harvesting systems, EPR is a critical parameter determining the system's viability. EPR manifests as the capacitor's self-discharge leakage current.

[0048] If the average power of the injected capacitor in the pre-stage micro-energy pump module is The current terminal voltage of the energy storage capacitor is Then the absolute physical inequality must be satisfied: ; If the above inequality does not hold, the leakage rate of the capacitor will be greater than the charging rate, the voltage will never reach the set wake-up threshold, and the system will be permanently deadlocked.

[0049] Therefore, this scheme mandates the use of multilayer ceramic capacitor (MLCC) arrays with ultra-high dielectric constants, or nanoampere-level self-leaking micro supercapacitors based on specific chemical systems (such as those based on improved barium titanate crystal structures), in the physical selection of the energy storage array. Its overall equivalent EPR must reach the level of hundreds of megaohms to gigohms at room temperature.

[0050] Hardware topology of a nanowatt-level deep subthreshold hysteresis comparator: To monitor the voltage of the energy storage capacitor and release the capacitor when a threshold is reached, the system incorporates an extremely low-power voltage monitoring chip. Conventional comparators consume microamps of current at rest, quickly draining the capacitor. The comparator used in this module has all its internal field-effect transistors biased in the deep subthreshold region.

[0051] In the subthreshold region, the gate-source voltage of the MOSFET Well below the activation threshold At this point, a conductive channel has not yet formed, and the current is generated by the diffusion of charge carriers rather than their drift. The drain current at this stage... and The current is exponentially small (typically a few picoamps to tens of picoamps). Utilizing this physical property, an internal bandgap reference source can provide an extremely stable internal reference voltage with an astonishingly low power consumption of less than 50 nA.

[0052] This comparator is configured with a purely hardware hysteresis window via an external pin: ; Set upper limit threshold (e.g., 3.0V) and lower limit shutdown threshold (For example, 2.2V). When the voltage of the energy storage capacitor crosses extremely slowly... At that moment, the positive feedback network of the Schmitt trigger inside the comparator flips instantaneously, outputting a steep logic high level to the load switch in the subsequent stage.

[0053] Miller capacitor soft start and surge control for load switches: When the hysteresis comparator outputs a high level, driving the subsequent load switch (essentially a P-MOSFET) to turn on, the subsequent stage connects to a large number of decoupling capacitors of the wireless communication module. If this P-MOSFET is momentarily fully turned on, it will generate a huge inrush current. As can be derived from the formula, this huge inrush current... This will cause a momentary voltage drop across the ESR of the energy storage capacitor. If this voltage drop causes the capacitor's terminal voltage to drop momentarily... The hysteresis comparator will immediately flip and turn off the switch.

[0054] This causes the system to enter a high-frequency "hiccup mode," where energy is wasted unnecessarily, and the radio frequency chip will never be able to start.

[0055] To mitigate this physical failure, the load switch of this invention integrates a slew rate control circuit based on the Miller effect. By artificially introducing a parallel integrating capacitor (Miller capacitance) between the gate and drain of the P-MOS, the time it takes for the transistor to travel from the cutoff region through the linear region to the saturation region is forcibly lengthened. This results in a smoothly rising conduction current, effectively limiting the maximum surge current to a milliampere level safety boundary, ensuring a smooth transition of the energy storage bus voltage, and securing a valuable, undisturbed startup voltage for the subsequent RF chips.

[0056] Module 4: Minimalist sniffing communication module, configured to instantly start using transient energy storage and the transient power supply window provided by the gating module, acquire external wake-up commands in space purely in hardware within a preset time before energy depletion, and output and latch a state holding signal to the BMS hardware forced start and bypass reset module before power failure.

[0057] When the load switch smoothly turns on, a large amount of sudden energy is instantly injected into the power supply rail of the wireless chip. At this point, the energy within the storage capacitor acts like a countdown hourglass, typically lasting only a few milliseconds to tens of milliseconds. Within this fleeting window, conventional IoT communication protocols (such as standard Zigbee or BLE handshake protocols) simply cannot execute in time. This module refactors the chip's underlying startup timing and electromagnetic wave decoding logic.

[0058] Pure hardware bare-metal boot sequence that avoids high-frequency crystal oscillators: Traditional RF devices typically require a wait time for an external high-precision, high-frequency quartz crystal oscillator (HFXO, e.g., 32MHz or 38.4MHz) to start and stabilize after power-on. Due to the piezoelectric mechanical inertia of the quartz crystal, this start-up process often takes 1ms to 5ms and consumes a significant amount of current. In our system, this waiting time is an unacceptable energy drain.

[0059] In terms of hardware configuration, this invention forces the startup clock source of the RF SoC to be bound to the chip's internal low-speed RC oscillator (LSI-RC). Although the frequency accuracy of the RC oscillator is extremely poor (temperature drift can reach ±5), its physical advantage is that it can start oscillating instantaneously within a few microseconds of power-on.

[0060] Meanwhile, upon power-up, the microcontroller kernel completely bypasses any bootloader or real-time operating system (RTOS) initialization. The program pointer jumps directly to a few lines of simplified assembly instructions preset in read-only memory (ROM). These instructions do not allocate a stack or initialize peripheral RAM; instead, they directly and forcefully overwrite the underlying control registers of the radio frequency physical layer (PHY) through pointer offsets to physical memory addresses.

[0061] Extreme optimization of the receiver front end and a signalless sniffing window: By overwriting the registers, the kernel forces the low-noise amplifier (LNA) and mixer of the RF front end to be enabled, directly entering the pure receive mode (RxOnly), and pulling the LNA gain to the maximum (sacrificing dynamic range for extreme sensitivity).

[0062] At this point, it is necessary to calculate the length of this precious "sniffing window." Assume the total capacity of the energy storage capacitor array is... The average current consumption of the radio frequency in extreme receiving mode is The duration of purely physical sniffing Satisfy the equation: ; For example, when the effective capacitance is 100μF, the voltage drop is 0.8V, and the receiving current is 5mA, the window period is only about 16ms.

[0063] Physical layer preamble capture based on hardware correlators: How to identify wake-up signals in a noisy electromagnetic environment without MAC layer software intervention? The transmitter (e.g., a handheld remote control used by maintenance personnel) continuously transmits a special physical layer broadcast packet that is not encapsulated by higher-level protocols. The core of this packet is an extremely long preamble sequence with specific pseudo-random characteristics. Inside the receiver's chip, a hardware correlator composed entirely of digital logic is directly connected to the baseband demodulator. When analog electromagnetic waves in space are received by the antenna, down-converted, sampled by the ADC, and quantized into a digital bitstream, the hardware correlator transmits this continuously flowing, unknown bitstream... The target synchronization word sequence is embedded in the silicon hardware register. Perform cross-correlation mathematical operations: ; in It is the length of the target sequence. It is the displacement over time.

[0064] This operation is performed entirely in parallel by logic gates on the silicon chip, without consuming any CPU clock cycles. Once the received bitstream within the sliding window closely matches the target sequence, the correlation function... The value will surge and exceed the preset decision threshold. This means, on a physical level, that the system has successfully "sniffed out" the wake-up command in a sea of ​​electromagnetic noise.

[0065] Asynchronous state retention and GPIO interrupt triggering: This is the RF chip's last struggle before it "dies" from energy depletion. When the correlator detects a peak, the hardware instantly generates an internal interrupt signal. This signal is directly routed to a special general-purpose input / output (GPIO) pin on the chip. The core physical design lies in the fact that the power domain of this specific GPIO pin must be physically isolated from the power domain of the RF core; it must belong to the chip's internal always-on domain or have a state latching function. When the pin is pulled high to output a high level, even if the voltage of the energy storage capacitor mercilessly drops below a certain threshold within the next millisecond... When the hysteresis comparator flips, the load switch cuts off the main power supply of the entire RF chip. This GPIO pin with latching function can still use a very small parasitic bypass capacitor attached to the outside of its pin to maintain the high level state symbolizing the "reset instruction" in the physical space for a few milliseconds to tens of milliseconds.

[0066] The extra momentary high level gained will be directly transmitted to the next module, the dormant main battery BMS, thereby reviving the entire high-power power supply system.

[0067] Module 5: BMS Hardware Force Startup and Bypass Reset Module, configured to be triggered by the status hold signal transmitted from the simplified sniffing communication module, utilizes the voltage relaxation effect after the main battery is deeply discharged and left to rest to conduct the controlled bypass, guides the advance current to trigger the main control MCU to power on and boot, and then the main control MCU takes over and forcibly releases the undervoltage lockout of the battery management system to restore the power supply of the entire system. When the BMS system shuts down the discharge MOSFET (D-FET) due to protection logic, the battery's positive and negative terminals exhibit high impedance to the outside world, and the main bus voltage is almost zero. The core technology of this module lies in utilizing the battery's electrochemical relaxation characteristics to reactivate the system through a controlled micropower bypass.

[0068] Utilization of battery voltage relaxation phenomenon: According to the Nernst equation and its deviation under kinetics, the battery will exhibit significant concentration polarization during continuous discharge due to the electrolyte concentration gradient and the delay in electrochemical reactions on the electrode surface.

[0069] When the BMS disconnects the load, the ions inside the battery begin to redistribute evenly, and the polarization potential gradually disappears. Physically, the battery terminal voltage slowly recovers from 2.5V (for lithium batteries) at the moment of disconnection to 2.8V–3.1V. Although this voltage recovery cannot support a large current, it is sufficient to drive the microcontroller (MCU) into its extremely low-power initial configuration state. The design premise of this module is to capture and utilize this "artificially high" but valuable electrical energy.

[0070] Logic level cascading and power bypass circuit: The GPIO latch signal from module four (wireless sniffing module) is a logic level with a voltage of approximately 2.8V~3.1V and very weak current capability. To drive the BMS system, this solution designs a two-stage cascaded trigger architecture: Primary trigger: Employs a sensitive-gate thyristor (SCR) or enhancement-mode N-MOSFET with an extremely low turn-on voltage. Its gate receives signals from the wireless module, its drain is connected to the positive terminal of the main battery, and a current-limiting resistor is connected in series with the source. Then connected to the system's main power supply bus ( ).

[0071] Current limiting and surge protection design: Because the battery is extremely weak at this time, the current limiting resistor... The value of this resistor is crucial. Its resistance must ensure that the current flowing into the system bus during a forced start-up is sufficient. This allows the main control MCU to reset without generating a battery internal resistance voltage drop exceeding 100mV, thus preventing the BMS's hard protection from being triggered again. The formula is expressed as: ; Physical connection point: The bypass is connected in parallel across the BMS discharge MOSFET (D-FET). It allows a very small amount of "precursor current" to enter the system.

[0072] Bootstrap takeover and BMS lockout of the main control MCU: When bypass is enabled, the system bus voltage... Upon lifting, the main control MCU receives a power-on reset signal (POR). At this point, the system enters the most critical bootstrap takeover sequence: Instruction Lock: Within the first 10 instruction cycles after the MCU powers on, a local GPIO pin must be pulled high immediately. This pin is connected to the primary flip-flop via a hardware OR gate logic, which is used to connect the wireless module's signal line. In this way, even if the wireless module shuts down due to depletion of the energy storage capacitor, the MCU can maintain the bypass conduction using the battery's own power, thus achieving "self-sustaining".

[0073] BMS software handshake: The MCU communicates with the BMS management chip via I2C or SMBus bus. It reads the internal status register of the BMS, identifies the current "undervoltage lockout" state, and sends a specific safety sequence instruction or forced enable instruction to command the internal charge pump of the BMS to restart the main discharge MOSFET.

[0074] Emergency mode switching: Once the main D-FET is turned on, the battery's high-current capability is restored. However, the MCU must limit the power consumption of the entire LED system at this time. It will configure the LED constant current driver to "intermittent blinking mode with an extremely low duty cycle (e.g., 0.1)" to serve as a visual emergency signal while ensuring that the average power consumption is lower than the battery's self-charging rate at extremely low charge levels (if there is ambient light).

[0075] The foregoing has only described certain exemplary embodiments of the present invention by way of illustration. Undoubtedly, those skilled in the art can modify the described embodiments in various ways without departing from the spirit and scope of the present invention. Therefore, the foregoing drawings and descriptions are illustrative in nature and should not be construed as limiting the scope of protection of the claims of the present invention.

[0076] It should be noted that, in this document, the use of relational terms such as "first" and "second" is merely for distinguishing one entity or operation from another, and does not necessarily require or imply any such actual relationship or order between these entities or operations. Furthermore, the terms "comprising," "including," or any other variations thereof are intended to cover non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such a process, method, article, or apparatus. Without further limitations, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, method, article, or apparatus that includes the element.

[0077] It should be understood that in the various embodiments of this application, the order of the above-mentioned processes does not imply the order of execution. The execution order of each process should be determined by its function and internal logic, and should not constitute any limitation on the implementation process of the embodiments of this application.

[0078] Those skilled in the art will recognize that the units and algorithm steps of the various examples described in conjunction with the embodiments disclosed herein can be implemented in electronic hardware, or a combination of computer software and electronic hardware. Whether these functions are implemented in hardware or software depends on the specific application and design constraints of the technical solution. Those skilled in the art can use different methods to implement the described functions for each specific application, but such implementation should not be considered beyond the scope of this application.

[0079] Those skilled in the art will understand that, for the sake of convenience and brevity, the specific working processes of the systems, devices, and units described above can be referred to the corresponding processes in the foregoing method embodiments, and will not be repeated here.

[0080] The units described as separate components may or may not be physically separate. The components shown as units may or may not be physical units; that is, they may be located in one place or distributed across multiple network units. Some or all of the units can be selected to achieve the purpose of this embodiment according to actual needs.

[0081] In addition, the functional units in the various embodiments of this application can be integrated into one processing unit, or each unit can exist physically separately, or two or more units can be integrated into one unit.

[0082] The above description is merely a specific embodiment of this application, but the scope of protection of this application is not limited thereto. Any variations or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in this application should be included within the scope of protection of this application. Therefore, the scope of protection of this application should be determined by the scope of the claims.

[0083] The foregoing has only described certain exemplary embodiments of the present invention by way of illustration. Undoubtedly, those skilled in the art can modify the described embodiments in various ways without departing from the spirit and scope of the present invention. Therefore, the foregoing drawings and descriptions are illustrative in nature and should not be construed as limiting the scope of protection of the claims of the present invention.

Claims

1. A wireless networked LED constant current charging and discharging management system, characterized in that, include: The optoelectronic multiplexing and state isolation module is configured to disconnect the LED light-emitting array from the main constant current drive controller and physically isolate the LED light-emitting array and switch it to the micro energy pump and collection module when the main battery is cut off due to undervoltage lockout triggered by power failure. The micro-energy pump and harvesting module is configured to receive the LED light-emitting array connected via the optoelectronic multiplexing and state isolation module, collect the reverse photogenerated voltage generated by the array under ambient light, and inject electrical energy into the transient energy storage and gating module after dynamic impedance matching and static current boosting. The transient energy storage and gating module is configured to store electrical energy from the micro-energy pump and collection module and monitor the voltage of the energy storage medium. When the voltage exceeds the set upper limit threshold, it instantly opens the gate to provide a controlled burst transient power supply window to the simplified sniffing communication module. The minimalist sniffing communication module is configured to instantly start using the transient energy storage and the transient power supply window provided by the gating module. It acquires external wake-up commands in the space within a preset time before the energy is exhausted, and outputs and latches a state holding signal to the BMS hardware forced start and bypass reset module before power failure. The MS hardware forced start and bypass reset module is configured to be triggered by the status hold signal transmitted from the simplified sniffing communication module. It utilizes the voltage relaxation effect of the main battery to conduct the controlled bypass, guides the advance current to trigger the main control MCU to power on and boot, and then the main control MCU takes over and forcibly releases the undervoltage lockout of the battery management system to restore power to the entire system.

2. The wireless networking LED constant current charging and discharging management system according to claim 1, characterized in that, The optoelectronic multiplexing and state isolation module includes a main cut-off tube M1 and an energy harvesting bypass tube M2; The anode of the LED light-emitting array is connected to the positive output terminal of the constant current drive controller, and its cathode is connected to node A; The main disconnect pipe M1 is connected between node A and the power ground loop, and the energy harvesting bypass pipe M2 is connected between node A and the input node B of the micro energy pump and harvesting module. The gates of the main cut-off tube M1 and the energy harvesting bypass tube M2 receive status indication signals converted by the system power rail voltage.

3. The wireless networking LED constant current charging and discharging management system according to claim 2, characterized in that, The main cut-off transistor M1 is a P-channel enhancement-mode MOSFET, and the energy harvesting bypass transistor M2 is a depletion-mode N-channel MOSFET or a low turn-on threshold enhancement-mode N-MOS. When in the deep sleep isolation state, the status indicator signal drops to 0V, the main cut-off transistor M1 is turned off and its parasitic diode is directed from the drain to the source to reverse the leakage current, the energy harvesting bypass transistor M2 is turned on, and the LED light-emitting array is physically connected to node B.

4. The wireless networking LED constant current charging and discharging management system according to claim 1, characterized in that, The micro-energy pump and harvest module uses a pure hardware fractional open-circuit voltage method for hardware maximum power point tracking; The micro-energy pump and harvest module includes a nanowatt-level low-frequency oscillator, a sample-and-hold capacitor, and a high-resistance voltage divider network. The nanowatt-level low-frequency oscillator periodically disconnects its input terminal to measure the absolute open-circuit voltage of the LED array. After being divided by a fixed ratio, the voltage is stored in the sample-and-hold capacitor as a reference voltage, which is used to dynamically adjust the equivalent input impedance.

5. The wireless networking LED constant current charging and discharging management system according to claim 4, characterized in that, The micro-energy pump and harvest module also includes an inductor boost topology or an asynchronous charge pump with extremely low quiescent current; The inductor boost topology is controlled by a hysteresis controller. When the input voltage exceeds the reference voltage, it outputs a very short conduction pulse to drive the input switch. The energy is then pumped to the transient energy storage and gating module through a miniature power inductor and a Schottky rectifier diode.

6. The wireless networking LED constant current charging and discharging management system according to claim 1, characterized in that, The transient energy storage and gating module includes: Energy storage medium composed of multilayer ceramic capacitor arrays or micro supercapacitors, and deep subthreshold hysteresis comparators; The deep subthreshold hysteresis comparator has its internal field-effect transistor biased in the deep subthreshold region. When it detects that the voltage of the energy storage medium slowly crosses the set upper limit turn-on threshold, it flips to output a high level. When the voltage drops to the lower limit turn-off threshold, it flips to output a low level.

7. The wireless networking LED constant current charging and discharging management system according to claim 6, characterized in that, The transient energy storage and gating module also includes a load switch with an internally integrated Miller capacitor soft-start circuit; The load switch is controlled by the output level of the deep subthreshold hysteresis comparator. The Miller effect is used to limit the surge current generated when power is supplied to the simplified sniffing communication module, preventing the voltage of the energy storage medium from dropping below the lower limit turn-off threshold momentarily.

8. The wireless networking LED constant current charging and discharging management system according to claim 1, characterized in that, The simplified sniffing communication module adopts a pure hardware bare-metal boot sequence. After power-on, it bypasses the bootloader program, starts oscillating quickly through the internal low-speed RC oscillator, and directly overwrites the RF physical layer registers, forcing the receiver front-end to enter pure reception mode. The wake-up command is captured by performing sliding cross-correlation calculation on the physical layer preamble in space using an internal hardware correlator, without any MAC layer software intervention.

9. A wireless network LED constant current charging and discharging management system according to claim 8, characterized in that, After the hardware correlator detects a relevant peak, the simplified sniffing communication module triggers an internal interrupt and pulls the state holding pin belonging to the normally open power domain high. The status holding pin is connected to an external parasitic bypass capacitor. Even after the transient power supply window ends and the main body of the communication module loses power, it can still maintain a high-level status holding signal for a preset duration to the BMS hardware forced start and bypass reset module.

10. A wireless network LED constant current charging and discharging management system according to claim 1, characterized in that, The BMS hardware forced start and bypass reset module adopts a two-stage cascaded trigger architecture, including a primary trigger and a current-limiting resistor; After receiving the state hold signal, the primary trigger turns on and leads the relaxation voltage of the main battery to the system bus through the current limiting resistor; After the system bus voltage is boosted, the main control MCU is triggered to power on and take over. The main control MCU outputs a lockout command to maintain bypass conduction and completes the BMS software handshake through the bus to forcibly release the undervoltage lockout state.

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