Internal switching control system for modular radio frequency electromagnetic generating device

Abstract

The application relates to the technical field of automatic control, in particular to an internal switching control system of a modular radio frequency electromagnetic generating device, which comprises a sampling initialization module, a residual energy calculation module, a latch parameter calculation module and a switching control module. After a front-stage signal source is turned off, the sampling initialization module acquires the voltage and current at the outlet end of a radio frequency channel. The residual energy calculation module adds the current detection sampling period residual energy representation quantity to the instant energy after the attenuation of the last detection sampling period residual energy representation quantity by using the energy dissipation variable of the current working frequency band and the detection sampling period. The latch parameter calculation module acquires a steady-state reflection coefficient as a latched reflection coefficient and calculates an electrothermal stress latching constant based on the initial output power, the power amplifier temperature rise characteristic and the cumulative thermal load. The switching control module corrects the basic safety energy threshold value based on the latched reflection coefficient, the electrothermal stress latching constant and the residual energy representation quantity to obtain a block safety threshold value, and outputs a control pulse to drive the radio frequency switch to switch when the threshold value is not greater than the threshold value. The application can effectively inhibit the contact transient arc discharge by dynamically correcting the safety threshold value.

Description

Technical Field

[0001] This invention relates to the field of automatic control technology, and in particular to the internal switching control system of a modular radio frequency electromagnetic generator. Background Technology

[0002] The internal switching control system of a modular radio frequency electromagnetic generator is a control device deployed inside the chassis of an electromagnetic compatibility test equipment. It coordinates the switching of multiple radio frequency switches between different signal paths. By issuing shutdown and drive commands, it manages the timing coordination between the front-end signal source, power amplifier, and radio frequency switches, and is a key component to ensure safe circuit switching in multi-frequency band and multi-standard testing tasks.

[0003] In existing technologies, automatic switching of multi-channel radio frequency signals is typically achieved using a switch control unit. However, during system operation, if the upstream signal source is not completely shut down or the residual energy of the power amplifier is not fully discharged before the switch is activated, it can easily lead to the risk of load switching and contact arcing. To address this, existing switching controls usually employ a cold switching method with a fixed time interval, i.e., after the signal source is shut down, a preset fixed delay is waited before the path switching is performed.

[0004] However, in actual operation, the residual energy dissipation trajectory of the energy storage components inside the power amplifier is often affected by the current operating conditions, exhibiting nonlinear and variable characteristics. Using a fixed time interval control method makes it difficult to adaptively match the differences in energy dissipation under different test conditions. For example, under certain high-power or low-frequency conditions, the energy dissipation period is relatively long, and the residual energy in the system may still be higher than the electrical safety insulation threshold at the end of the preset fixed delay, resulting in a weak transient arc when the RF switch operates. This phenomenon can easily accumulate in long-term, frequently switching test tasks, adversely affecting the physical lifespan of the RF switch contacts and the long-term switching reliability of the system. Summary of the Invention

[0005] To address the technical problem that existing fixed-delay switching control systems struggle to adaptively match the differences in residual energy dissipation under different frequency bands and power conditions, leading to RF switches operating in an insufficiently discharged state and causing contact transient arcing and erosion, this invention provides an internal switching control system for a modular RF electromagnetic generator. This system includes the following modules:

[0006] The sampling initialization module is used to receive the path switching command and shut down the previous signal source, obtain the current working frequency band, initialize the residual energy characterization quantity, and obtain the voltage and current at the output end of the radio frequency path in each detection sampling period. The residual energy calculation module is used to take any detection sampling period as the current detection sampling period, use the energy dissipation variable of the current working frequency band and the detection sampling period to attenuate the residual energy characterization of the previous detection sampling period to obtain the historical residual energy, and add it to the voltage, current and instantaneous energy determined based on the current detection sampling period to obtain the residual energy characterization of the current detection sampling period. The latching parameter calculation module is used to obtain the steady-state reflection coefficient of the RF path as the latching reflection coefficient at the instant the front-end signal source is turned off; and to calculate the electrothermal stress latching constant based on the initial output power of the RF path, the temperature rise characteristics of the power amplifier corresponding to the RF path, and the cumulative heat load generated by the continuous operation of the power amplifier. The switching control module is used to correct the preset basic safety energy threshold to obtain the blocking safety threshold based on the latch reflection coefficient, electrothermal stress latch constant and the residual energy characterization of the current detection sampling period; when the residual energy characterization is not greater than the blocking safety threshold, the output control pulse drives the RF switch to switch.

[0007] The system described in this invention, after shutting down the pre-amplifier signal source, acquires the voltage and current at the output of the RF path during the detection sampling period and performs attenuation calculations based on the energy dissipation variables of the current operating frequency band to obtain the historical residual energy, which is then used to calculate the corresponding real-time residual energy characterization online. Simultaneously, this invention combines the steady-state reflection coefficient latched at the moment of shutdown with the initial output power, the temperature rise characteristics of the power amplifier, and the accumulated heat load to calculate the electrothermal stress latching constant to dynamically correct the basic safe energy threshold. This allows for dynamic adjustment of the switching criteria under complex and variable operating conditions and the acquisition of a blocking safety threshold that fits the actual electrothermal boundary. This ensures that the control pulse is output only when the residual energy characterization is not greater than the blocking safety threshold to drive the RF switch switching, thereby suppressing transient arc discharge between contacts and reducing the probability of physical damage to the switching control system and RF switch caused by load switching.

[0008] Preferably, the step of using the energy dissipation variable of the current operating frequency band and the detection sampling period to attenuate the residual energy characterization of the previous detection sampling period to obtain the historical residual energy includes: calculating the product of the energy dissipation variable of the current operating frequency band and the detection sampling period, adding the product to a preset constant to obtain an attenuation factor; and dividing the residual energy characterization of the previous detection sampling period by the attenuation factor to obtain the historical residual energy.

[0009] This invention calculates the attenuation factor by multiplying the energy dissipation variable of the current operating frequency band by the detection sampling period and adding a preset constant. Then, it obtains the historical residual energy by dividing the residual energy characterization of the previous detection sampling period by the attenuation factor. This directly maps the physical attenuation characteristics of the operating frequency band to the numerical recursion process, reducing the energy residual deviation problem caused by the lack of frequency band adaptability due to fixed delay.

[0010] Preferably, obtaining the residual energy characterization of the current detection sampling period includes: multiplying the voltage, current and detection sampling period of the current detection sampling period to obtain the instantaneous energy; and adding the instantaneous energy to the historical residual energy to obtain the residual energy characterization of the current detection sampling period.

[0011] This invention calculates the instantaneous energy by multiplying the voltage, current and the current sampling period of the current detection sampling period, and then adds it to the historical residual energy to obtain the residual energy characterization of the current detection sampling period. This is used to dynamically track the single-step active residual injection energy at the numerical recursion level, thereby improving the dispersion of the initial total energy assessment during the passive discharge period.

[0012] Preferably, the calculation of the electrothermal stress latching constant based on the initial output power of the radio frequency path, the temperature rise characteristics of the power amplifier corresponding to the radio frequency path, and the cumulative heat load generated by the continuous operation of the power amplifier includes: multiplying the initial output power of the radio frequency path, the temperature rise characteristics of the power amplifier corresponding to the radio frequency path, and the cumulative heat load generated by the continuous operation of the power amplifier to obtain the electrothermal stress latching constant.

[0013] This invention calculates the electrothermal stress latching constant by multiplying the initial output power of the radio frequency path, the temperature rise characteristics of the power amplifier, and the cumulative thermal load. This constant is used to characterize the electrothermal stress characteristics at the moment of turn-off in a multidimensional way, providing a deterministic physical reference for the adaptive correction of the subsequent blocking safety threshold.

[0014] Preferably, obtaining the temperature rise characteristics of the power amplifier includes: obtaining the initial ambient temperature and the turn-off transient temperature of the pre-amplifier signal source at the moment of shutdown; calculating the difference between the turn-off transient temperature and the initial ambient temperature, and using the ratio of the difference to the initial ambient temperature as the temperature rise characteristics of the power amplifier.

[0015] Preferably, the acquisition of the cumulative heat load generated by the continuous operation of the power amplifier includes: acquiring the total continuous operating time of the power amplifier in the active state; calculating the ratio of the total continuous operating time to a preset reference time constant to obtain a time normalized value; calculating the product of the time normalized value and a preset frequency thermal coupling variable of the current operating frequency band, and adding a preset constant to obtain the cumulative heat load generated by the continuous operation of the power amplifier.

[0016] Preferably, the step of correcting the preset basic safety energy threshold to obtain the blocking safety threshold based on the latch reflection coefficient, the electrothermal stress latch constant, and the residual energy characterization of the current detection sampling period includes: dividing the residual energy characterization of the current detection sampling period by the reference energy constant to obtain an energy normalization value; dividing the electrothermal stress latch constant by the reference power constant to obtain a stress normalization value; calculating the product of the energy normalization value and the latch reflection coefficient; adding the product to the stress normalization value and the preset constant to obtain a threshold correction factor; and dividing the basic safety energy threshold corresponding to the current operating frequency band by the threshold correction factor to obtain the blocking safety threshold.

[0017] This invention obtains the energy normalization value and stress normalization value by dividing the residual energy characterization value and the electrothermal stress latching constant by the reference constant, respectively. The product of the energy normalization value and the latching reflection coefficient is added to the stress normalization value and the preset constant to calculate the threshold correction factor. Then, the basic safe energy threshold is divided by the threshold correction factor to obtain the blocking safety threshold. This is used to dynamically balance the influence of mismatch reflection and accumulated heat load on the switch withstand limit, reducing the risk of load-induced false switching when the test conditions change abruptly.

[0018] Preferably, the step of outputting a control pulse to drive the RF switch switching when the residual energy characterization is not greater than the blocking safety threshold includes: obtaining the residual energy change rate based on the residual energy characterization of adjacent detection sampling periods; and outputting a control pulse to drive the RF switch switching when the residual energy characterization of the current detection sampling period is not greater than the blocking safety threshold and the residual energy change rate is not greater than a preset convergence boundary.

[0019] Preferably, obtaining the residual energy change rate includes: calculating the difference between the residual energy characterization value of the previous detection sampling period and the residual energy characterization value of the current detection sampling period to obtain the single-step energy dissipation value; dividing the single-step energy dissipation value by the detection sampling period to obtain the residual energy change rate.

[0020] Preferably, the initialization of the residual energy characterization quantity includes: setting the initial value of the residual energy characterization quantity to 0 at the initial moment when the preceding signal source is turned off.

[0021] The beneficial effects of this invention are as follows: This invention obtains the voltage and current at the output end of the RF path during the detection sampling period and performs real-time calculations based on energy dissipation variables. This dynamically acquires residual energy characteristics that accurately recreate the passive discharge state, enabling accurate tracking of the nonlinear energy dissipation trajectory. This improves upon the shortcomings of traditional fixed-delay control methods, which cannot adaptively match attenuation differences across different frequency bands. This invention dynamically adjusts the blocking safety threshold by integrating the latching reflection coefficient of the RF path, initial output power, and the temperature rise characteristics and accumulated thermal load of the power amplifier. This directly incorporates multidimensional electrothermal boundary stress into the switching control criterion, reducing the probability of insulation failure under complex high-power or low-frequency operating conditions. This invention introduces the residual energy change rate and convergence boundary for dual steady-state verification. Control pulses to drive the RF switch are only output when the residual energy amplitude meets the standard and the attenuation slope tends to converge. This ensures the system's ability to withstand transient glitches during electromagnetic compatibility testing and reduces contact erosion damage caused by the accumulation of weak transient arcs. Attached Figure Description

[0022] Figure 1 A detailed structural block diagram of the internal switching control system of the modular radio frequency electromagnetic generator provided in the embodiments of the present invention; Figure 2 A block diagram of the internal switching control system of the modular radio frequency electromagnetic generator provided in an embodiment of the present invention. Detailed Implementation

[0023] This invention provides an internal switching control system for a modular radio frequency electromagnetic generator, such as... Figure 1 As shown, the internal switching control system of the modular radio frequency electromagnetic generator uses a processor as the core control unit. The processor is bidirectionally connected to the memory for data and instruction access. The processor connects to an external control terminal via a communication bus to receive path switching commands and is also connected to a high-speed analog-to-digital converter, a timing controller, and digital input / output channels. The processor's physical quantity input terminals are connected to a temperature sensor, a voltage transformer, and a current transformer to capture the physical parameters at the radio frequency path output in real time. The system's underlying radio frequency main link consists of a pre-amplifier, a power amplifier, and a radio frequency switch connected in series. The processor outputs control pulses to the radio frequency switch based on parameter calculation results to drive path switching, and a power meter module provides auxiliary monitoring of the output status of the radio frequency switch.

[0024] like Figure 2 As shown, the internal switching control system of the modular radio frequency electromagnetic generator according to this embodiment of the invention includes a sampling initialization module 100, a residual energy calculation module 200, a latching parameter calculation module 300, and a switching control module 400. The sampling initialization module 100 is used to receive the path switching command and shut down the previous signal source, obtain the current working frequency band, initialize the residual energy characterization quantity, and obtain the voltage and current at the output end of the radio frequency path in each detection sampling period.

[0025] It should be noted that when the radio frequency electromagnetic generator switches frequency bands, a significant amount of electromagnetic energy remains in the passive components such as the energy storage inductors and distributed capacitances of the power amplifiers at each stage inside the device. In order to provide a definite time starting point and parameter benchmark for the subsequent accurate assessment of the dissipation boundary of the residual energy and the thermal legacy of the chassis, it is necessary to capture a series of initial boundary conditions and inherent hardware sampling configurations of the device in real time while shutting down the external excitation source, to ensure the correctness of the boundary conditions in subsequent calculations.

[0026] First, the switching command and basic test configuration parameters are acquired. Specifically, after receiving the path switching command from the external control terminal, the control system first sends a shutdown command to the upstream signal source within the system to block the continuous injection of radio frequency energy. Simultaneously, the control system reads the current test configuration parameters via the bus, which include the current operating frequency band and initial output power. The control system also reads the current initial ambient temperature value through a temperature sensor located inside the power amplifier chassis and locks the current state of the radio frequency switch.

[0027] Then, the system configures and acquires baseline parameters and state data streams for dynamic estimation of residual energy and threshold correction. It should be noted that, considering the rapid decay of residual electromagnetic energy in the passive network inside the power amplifier at the microsecond level after the pre-amplifier signal source is turned off, and the heterogeneity of skin effect and dielectric loss at different operating frequency bands, the system needs to simultaneously acquire high-resolution detection sampling period, instantaneous voltage and current, and energy dissipation variables with attenuation rate correction specific to the frequency band. Simultaneously, to eliminate the physical dimension barriers in subsequent cross-dimensional algebraic synthesis and prevent safety boundary divergence, the system simultaneously acquires baseline unit energy scale constants, baseline unit power scale constants, and baseline running time constants with standard dimension alignment capabilities; and dynamically loads the basic nominal safe power threshold, frequency thermal coupling variables, and convergence threshold boundaries used to define safety and noise boundaries, thereby providing dimensionless underlying data support for subsequent dynamic recursion of residual energy and adaptive bidirectional threshold approximation.

[0028] Specifically, the control system activates its internal high-speed analog-to-digital converter and timing controller, configuring the detection sampling period to a microsecond-level discrete time step that matches the electromagnetic discharge attenuation rate of the matching network inside the target power amplifier. This ensures a high-resolution timing capture channel for the rapid electromagnetic discharge process within the hardware interruption period. Simultaneously, the control system loads hard-coded reference unit energy scale constants, reference unit power scale constants, and reference running time constants from its internal non-volatile memory. These values ​​are all fixed at 1.0, with physical units defined as joules, watts, and seconds, respectively. The control system further retrieves the pre-stored frequency band-dissipation rate mapping matrix and hardware characteristic table based on the current operating frequency band, dynamically reading the basic nominal safe power threshold, energy dissipation variable, frequency thermal coupling variable, and preset convergence threshold boundary for that specific frequency band. It also activates the continuous data acquisition channel of the voltage and current transformers, acquiring and continuously outputting the voltage and current at the RF path output in real time during each detection sampling period after the signal source is turned off. Simultaneously, at the initial switching point when the signal source is turned off, i.e., the number of detection sampling periods… At that time, the control system will use the initial residual energy characterization quantity Set to 0 and wait for the residual energy and environmental status assessment to be completed.

[0029] The residual energy calculation module 200 is used to take any detection sampling period as the current detection sampling period, use the energy dissipation variable of the current working frequency band and the detection sampling period to attenuate the residual energy characterization of the previous detection sampling period to obtain the historical residual energy, and add it to the voltage, current and instantaneous energy determined based on the current detection sampling period to obtain the residual energy characterization of the current detection sampling period.

[0030] It should be noted that during the passive dissipation period after the pre-amplifier signal source is turned off, the actual release trajectory of the residual electromagnetic energy inside the amplifier exhibits a highly nonlinear hyperbolic decay characteristic. To smoothly track the residual energy characteristic value within the current path while maintaining low processor computational overhead, this invention constructs a first-order time-domain recursive iterative algorithm at the pure scalar algebra level. This algorithm utilizes a single-step time damping term in the denominator to progressively attenuate and spread the historical state, and dynamically superimposes it with the instantaneous energy micro-element of the current period. This achieves efficient dynamic tracking of residual energy with strictly constant computational complexity.

[0031] Based on the above logic, the first Residual energy characterization of each detection sampling cycle Satisfying the relation: ; in, For the first The residual energy characterization of each detection sampling cycle; For the first The residual energy characterization of each detection sampling cycle; For the first The voltage corresponding to each detection sampling cycle; For the first The current of each detection sampling cycle; To detect the sampling period; This represents the energy dissipation variable for the current operating frequency band.

[0032] In this relation, This represents the single-step time-damped attenuation factor, due to the dissipation of variables. Always positive, and the detection sampling period The value of this damping denominator is always greater than 1, thus ensuring that the historical cumulative representation of the previous cycle is monotonically reduced as the time step is advanced. This mathematical topology, after adaptive recursive expansion on the macroscopic time axis, effectively realizes that the further back the historical power consumption is, the more effective it is in relation to the current... The contribution of the physical effect decreases geometrically with time difference, approaching 0. This constitutes the micro-element of the instantaneous energy release actually measured within the current detection cycle. It should be clearly stated that... This is not the physical integral of the remaining absolute energy within the chassis, but rather an equivalent evaluation metric characterizing the energy dissipation hysteresis of the RF path during the passive discharge period. The formula employs a first-order differential recursive structure, where the calculation of the current cycle at the hardware level depends solely on the scalar result of the previous cycle. The dynamic snapshot acquisition in the current cycle eliminates the systemic risk of a linear surge in the historical data throughput overhead of the microcontroller as the test time lengthens, ensuring that the algorithm effectively avoids the risk of computational timing lag within the microsecond-level extreme control cycle. As the current sampling count monotonically increases, since the active injection power has been turned off in the previous stage and the historical retention state continues to monotonically decrease under the constraint of the passive attenuation factor in the previous stage, the residual energy characterization calculated by the entire relational formula shows a relatively smooth decreasing characteristic after an initial short period of cumulative increase.

[0033] The construction of this relation originates from the damping discharge law of passive electromagnetic energy storage networks and the state-space relaxation evolution of discrete-time systems. In the RF transmission cable and the final stage matching network of the power amplifier after power failure, the attenuation of residual electromagnetic energy is not constant, but is strongly constrained by the impedance of the distributed capacitance-inductance discharge circuit. Its energy attenuation in the discrete domain better conforms to the first-order fractional time-damped relaxation curve. Therefore, the above inverse proportional iterative fraction is constructed as a time-domain damping constraint term. At the same time, since the total residual energy is represented by the algebraic evolution of the energy released in each historical tiny discharge time slice on the time axis, an instantaneous scalar multiplication term of the current power consumption element is introduced. Using the dynamic attenuation modulation of this single-step recursive factor, the non-monotonic energy discharge deviation caused by high-frequency skin effect, matching capacitor dielectric loss, and anisotropic distribution parameters within the RF path can be corrected.

[0034] It should be noted that the testing sampling cycle and energy dissipation variables The configuration is well-suited to the inherent sampling bandwidth of the RF generator and the network impedance matching characteristics at different frequency bands: For high-frequency test scenarios with small energy storage capacity, electromagnetic energy dissipates quickly, and a smaller detection sampling period is used in the sampling initialization module 100. And match a large energy dissipation variable. This enhances the sensitivity to capturing faster energy decay curves; for test scenarios with a high proportion of low-frequency, high-power energy storage components, energy decay is relatively slow, which can be addressed by increasing the detection sampling period. And reduce energy dissipation variables This improves adaptability to long-period tail energy dissipation patterns. In this embodiment, the control system directly calls the microsecond-level discrete time step configured in the sampling initialization module 100, which matches the electromagnetic dissipation attenuation rate of the matching network, as the detection sampling period. Energy dissipation variables The values ​​are between [values] in different frequency bands according to the characteristic mapping table. to Between these, the residual energy characterization of the current cycle is finally dynamically calculated and output.

[0035] Thus, the residual energy characterization of each detection sampling cycle was obtained.

[0036] The latching parameter calculation module 300 is used to obtain the steady-state reflection coefficient of the RF path as the latching reflection coefficient at the instant the front-end signal source is turned off; and to calculate the electrothermal stress latching constant based on the initial output power of the RF path, the temperature rise characteristics of the power amplifier corresponding to the RF path, and the cumulative heat load generated by the continuous operation of the power amplifier.

[0037] It should be noted that the passive energy dissipation process of the power amplifier corresponding to the RF path is usually completed within microseconds to milliseconds. Within this short timescale, the macroscopic thermal state inside the chassis is in a period of significant thermal hysteresis and stability, and its temperature will not continue to rise non-physically after the loss of the preceding stage excitation. At the same time, once the signal source is turned off, the forward and reflected power in the RF path will instantly drop into the hardware noise floor. If dynamic reflection coefficient measurement is continued at this time, it will lead to a serious deterioration of the receiver's signal-to-noise ratio, and the calculated reflection coefficient will inevitably undergo drastic random divergence and jumps.

[0038] First, acquire the temperature and operating time data of the power amplifier corresponding to the RF path during the shutdown transient. It should be noted that, considering the absolute instant of the front-end signal source shutdown, the heat in the internal microenvironment of the chassis has not yet diffused extensively to the external heat dissipation path. The temperature state at this node can accurately and without distortion map the final heat accumulation of the entire active transmission stage, thus avoiding interference from subsequent heat conduction hysteresis and temperature fluctuations after shutdown, ensuring the absolute solidification of boundary conditions. Simultaneously, since the deep thermal saturation degree of the power devices inside the system is strongly correlated with the duration of active operation, it is necessary to accurately characterize the depth of accumulated heat load caused by continuous high-load operation through a precise time scale. Therefore, it is essential to simultaneously capture the temperature state and time span at the start of the signal source disconnection, providing a high-fidelity raw data foundation for subsequent accurate assessment of electrothermal stress.

[0039] Specifically, at the instant the front-end signal source is shut down, the control system uses a temperature sensor located inside the power amplifier chassis to capture and lock the instantaneous shutdown temperature value in real time. Simultaneously, the control system reads its internal high-precision timing counter to obtain the total dynamic continuous operating time span in the active state. It should be noted that the active state refers to the normal transmission phase where, before the front-end signal source is shut down, the RF electromagnetic generator is continuously injected with external RF energy and the power amplifier is in load-bearing output mode. Correspondingly, after the control system issues a command to shut down the front-end signal source, the device enters a passive dissipation period where residual electromagnetic energy is naturally discharged through internal passive components such as energy storage inductors and distributed capacitors.

[0040] Next, the electrothermal stress latching constant is calculated. It should be noted that after high-power active emission, the internal passive energy storage network and the physical thermal resistance boundary of the RF electromagnetic generator are in a state of deep electrothermal coupling. To establish a static reference that does not dynamically drift during the passive discharge process, the thermal stress reflected by the spatial temperature rise ratio and the accumulated thermal saturation depth over time must be scalarized and solidified. This cross-dimensional electrothermal state constant latching provides a basis for subsequent integration with discrete dynamic residual energy characterization. Safety boundary assessment provides a definite and quantifiable benchmark for the thermal legacy of the equipment environment, thereby effectively avoiding subsequent passive discharge calculations from falling into threshold misjudgment due to the lack of chassis background thermal stress constraints.

[0041] Based on the above logic, the electrothermal stress latching constant satisfies the following relationship: ; in, The latch-up constant for the thermal stress of the power amplifier; The initial output power of the radio frequency electromagnetic generator before the path switching; This represents the power amplifier's transient temperature at the moment the signal source is turned off. This is the initial ambient temperature value; The total dynamic continuous operating time span of the equipment before the upstream signal source is shut down; For the current operating frequency band The frequency thermal coupling variable; This is the baseline operating time constant.

[0042] In this relation, Used to calculate the macroscopic temperature rise ratio of the chassis during active testing, since the laboratory ambient temperature is always much greater than absolute 0 degrees, the risk of 0 value overflow is effectively avoided when it is used as a denominator in the calculation. To calculate the cumulative heat load depth resulting from continuous high-load operation, an arithmetic ratio elimination method is used to eliminate the time dimension by introducing a reference operating time constant and performing arithmetic ratio elimination on the actual total dynamic continuous working time span. This transforms the time dimension into a purely dimensionless thermal saturation weighted gain, which is then corrected for frequency band specific weights by a frequency thermal coupling variable. The above two items are multiplied by the initial output power by a scalar, ensuring that the physical dimension of the electrothermal stress latching constant is absolutely aligned with the initial output power, converging and solidifying into the power dimension. This topological structure ensures that when any of the relative temperature rise ratio, total working time span, or initial output power increases, the calculated electrothermal stress latching constant exhibits a clear monotonically increasing characteristic, latching the environmental thermal stress legacy left at the moment of shutdown. This value remains fixed as a static known quantity throughout the subsequent residual energy release calculation.

[0043] Meanwhile, considering that the reflected power of the path will be quickly overwhelmed by thermal noise after the active circuit is disconnected, the control system reads and captures the steady-state dynamic reflection coefficient under active operation through the power meter module integrated in the radio frequency path at the last moment before issuing the shutdown command, and locks it as the latched reflection coefficient. The latching reflection coefficient The value is in arrive It fluctuates between these values ​​and has no physical dimensions. This latching reflection coefficient As a static, known constant, it remains fixed throughout the subsequent residual energy discharge calculation and is used to correlate and weight with dynamic residual energy in subsequent modules. This allows for a true characterization of the safety threat to energy retention posed by the severity of the physical impedance mismatch between the current RF path and the load while maintaining a high signal-to-noise ratio.

[0044] The construction of this relationship originates from the electrothermal evolution of Fourier's law of solid-state thermal conduction and the thermal resistance and damping characteristics of high-frequency power amplifier transistors. Inside the sealed modular RF generator chassis, heat accumulation and dissipation are not instantaneous and synchronous. The conduction of transistor junction temperature to the heat sink and ambient air exhibits a significant millisecond-level delay, and the thermal accumulation state at the moment of turn-off better conforms to the nonlinear coupling curve of initial power and temperature rise step. Therefore, a relative temperature rise ratio is constructed as a temperature field constraint term, and the total dynamic continuous operating time span is introduced. The resulting thermal saturation weighting term; simultaneously, to correct for differences in operating frequency bands The varying drain efficiencies of the transistors inside the amplifier, the uneven airflow distribution within the chassis, and the thermomechanical uncertainties caused by the positional deviation of the thermistor introduce frequency-thermal coupling variables. The time term is weighted and adjusted. By using the transient static latching of this electrothermal composite factor, the macroscopic environmental thermal stress legacy remaining from the active emission testing phase can be accurately assessed and solidified.

[0045] It should be noted that the above-mentioned frequency thermal coupling variables The value of the parameter is closely matched with the chassis material, heat sink fin area, and the physical thermal resistance curve of the power amplifier in the current test frequency band: For RF systems with poor heat dissipation and low operating efficiency in the high-frequency band, the amplifier generates a lot of heat. By pre-configuring a larger frequency thermal coupling variable for this frequency band in the sampling initialization module 100, the appropriate parameter is determined. The base value can increase the weight of the assessment of stress that worsens heat dissipation; for RF systems equipped with powerful air cooling or high efficiency in the low-frequency band, the frequency thermal coupling variable can be appropriately reduced. The value of . In this embodiment, the control system directly reuses the specific characteristic parameters loaded in the sampling initialization module 100, whose frequency thermally coupled variables. The algebraic values ​​of the values ​​in different frequency bands are between to In the end, the constant electrothermal stress latch-up constant was calculated in one step. and latching reflection coefficient It continuously outputs data to subsequent modules.

[0046] Thus, the electrothermal stress latching constant and the latching reflection coefficient were obtained.

[0047] The switching control module 400 is used to correct the preset basic safety energy threshold to obtain the blocking safety threshold based on the latch reflection coefficient, the electrothermal stress latch constant and the residual energy characterization of the current detection sampling period; when the residual energy characterization is not greater than the blocking safety threshold, the output control pulse drives the radio frequency switch to switch.

[0048] It should be noted that when switching, the ability of the RF switch to withstand load breakdown depends not only on the instantaneous residual power of the path, but also on the strong combined constraints of the voltage standing wave ratio caused by the impedance mismatch of the current path and the decrease in dielectric insulation strength of the mechanical contact surface due to long-term high temperature.

[0049] First, the dynamically corrected blocking safety threshold is calculated. It's important to note that to overcome the linear subtraction overflow caused by traditional one-dimensional threshold reduction, or the physical boundary divergence caused by multi-dimensional coefficient multiplication structures, the electromagnetic matching stress and environmental thermal resistance stress affecting contact gap electrical breakdown must be integrated across dimensions into the same mathematical topology. By constructing an inverse proportional denominator cooperative topology, dynamic residual energy is used as the sole independent variable, along with the aforementioned latched electrothermal and mismatch constants, as the denominator. This allows for the amplification of the denominator using the large residual energy during the initial switching phase, achieving a deep downward compression of the safety threshold and rigidly maintaining the absolute electrical safety blocking window. In the later stages of energy dissipation, as the denominator monotonically contracts due to energy decay, it guides the safety threshold to adaptively and monotonically rise, forming a dynamic bidirectional approximation with the energy reduction trajectory. This maximizes the timeliness of channel switching while ensuring insulation safety.

[0050] Based on the above logic, using the collaborative threshold correction formula, the first... The blocking safety threshold, corrected for each detection sampling period, satisfies the following relationship: ; in, For the target RF switch in the first The blocking safety threshold for each detection sampling cycle; For the target RF switch in the current operating frequency band The basic nominal safe power threshold is obtained by retrieving the physical tolerance limit curve of the RF switch in the current frequency band. The latching reflection coefficient; For the first The normalized value of the residual energy characterization of the first detection sampling period is obtained by using the first... The residual energy characterization of each detection sampling cycle is calculated by dividing it by the preset reference unit energy scale constant; The normalized value of the electrothermal stress latch-up constant of the power amplifier during the shutdown transient is calculated by dividing the overall electrothermal stress latch-up constant of the power amplifier chassis during the shutdown transient by a preset reference unit power scale constant.

[0051] In this formula, the normalized value of the residual energy characterization quantity is multiplied by the latching reflection coefficient. This multiplication is used to amplify the denominator with a larger energy value during the initial stage of pre-shutdown, thereby increasing the overall blocking safety threshold. Deep compression to near zero creates a rigid, cold-switching electrical blocking space; the normalized value of the electrothermal stress latch-up constant is used to stabilize the overall slope of the threshold rise based on previous thermal legacy. When As it monotonically decreases over time, its normalized value monotonically shrinks, guiding the final output blocking safety threshold. The adaptive monotonic recovery forms a dynamic bidirectional approximation with the energy-decreasing trajectory.

[0052] The construction of this equation originates from the feedback mechanism of standing wave energy distribution in electromagnetic wave transmission lines and the nonlinear evolution of the electrical breakdown criterion for high-frequency contact gap insulation. Whether a loaded arc discharge can occur in the tiny gas gap inside an RF switch directly depends on the peak value of the transient voltage applied across the terminals and the temperature rise on the electrode surface caused by high-load operation. Therefore, this invention constructs an inverse proportional fractional topology, placing the electromagnetic mismatch stress term and the environmental thermal resistance stress term together in the denominator to evaluate the algebraic depth compression of the safety boundary caused by voltage standing wave superposition and gas insulation strength reduction.

[0053] Next, the rate of change of residual energy is calculated. It should be noted that in actual electromagnetic compatibility (EMC) testing environments, complex conducted and radiated transient interferences can easily introduce high-frequency negative pulse spikes into the sampling channel. This can cause a non-physical downward jump in the calculated dynamic energy integral value at an isolated point, resulting in a false amplitude false-compliance phenomenon. Relying solely on amplitude criteria can easily lead to false triggering under load. Therefore, a first-order algebraic difference operator must be introduced to extract the time derivative trajectory of the residual energy. Utilizing the physical characteristic that unsteady-state noise spikes have a high time derivative on the time axis, random high-frequency spikes are transformed into significant numerical spikes. This approach can accurately identify the true steady-state energy dissipation tail and external interference spikes, establishing a highly reliable dynamic evaluation index for trend coordination judgment.

[0054] Specifically, the control system uses simple algebraic difference calculations between adjacent cycles to obtain the first... Residual energy change rate per detection sampling cycle residual energy change rate Satisfying the relation: ; in, For the target RF switch in the first The rate of change of residual energy in each detection sampling cycle; For the first The residual energy characterization of each detection sampling cycle; For the first The residual energy characterization stored in each detection sampling cycle; This is the preset detection sampling period.

[0055] In this relation, The monotonically dissipated difference of residual energy between adjacent sampling periods, divided by the time resolution. The resulting rate of change of residual energy represents the absolute value of the slope of the tangent to the trajectory of residual energy dissipation. This term is used to assess whether the energy dissipation curve has truly entered a steady-state period. On a one-dimensional ideal decay curve, the energy approaching 0 must be accompanied by its slope approaching 0.

[0056] Finally, the control system executes a dual-judgment gate logic for the output of the control pulse, considering both amplitude and trend conditions: it determines whether the ratio of the residual energy representation to the baseline operating time constant is less than or equal to the blocking safety threshold, and whether the residual energy change rate is less than or equal to the preset convergence threshold boundary. If either of these conditions is not met, such as noise glitches causing the equivalent residual power to falsely meet the standard while the residual energy change rate overshoots and surges, the trend auxiliary gate locks the output state through a veto mechanism. The control system determines that there is a risk of transient instability, maintains the locked state, and the control system enters the next detection and sampling cycle. The system then returns to repeatedly execute the residual energy calculation module 200 to the switching control module 400. When both of the above conditions are simultaneously met, the control system determines that the absolute cold switching electrical safety boundary locked by fractional bidirectional approximation has been reached, and that high-frequency noise and tail oscillations have been filtered by the trend gate. The energy dissipation trajectory has truly entered a steady-state convergence period with a slope approaching 0. Subsequently, the system controls the internal digital input / output channel to output a high-level control pulse. This control pulse directly acts on the drive coil of the target RF switch, driving the RF switch to perform mechanical contact switching and completing the RF path switching.

[0057] It should be noted that the convergence threshold boundary Reference unit energy scale constant and reference unit power scale constant The value needs to be set based on the inherent mechanical delay of the RF switch driver mechanism and the background interference level at the test site: for sampling scenarios with strong background interference and fragile switch contacts, the value should be reduced. The value of is set to increase the stringency of the judgment on trend steady-state conditions, forcing a smooth energy dissipation curve; for operating conditions with a clean background environment and relatively rapid switching action, the value can be appropriately relaxed. In this embodiment, The control software is hard-coded as follows ; The control software hard-coded it as a fixed algebraic constant. Convergence threshold boundary Preferred .

[0058] This completes the passive safety blocking and cold switching control of the radio frequency path.

[0059] The internal switching control system of the modular radio frequency electromagnetic generator also includes other components well known to those skilled in the art, such as communication buses and communication interfaces. Their setup and functions are known in the art and will not be described in detail here.

[0060] The above are all preferred embodiments of the present invention and are not intended to limit the scope of protection of the present invention. Therefore, all equivalent changes made in accordance with the structure, shape and principle of the present invention should be covered within the scope of protection of the present invention.

Claims

1. An internal switching control system for a modular radio frequency electromagnetic generator, characterized in that, The system includes the following modules: The sampling initialization module is used to receive the path switching command and shut down the previous signal source, obtain the current working frequency band, initialize the residual energy characterization quantity, and obtain the voltage and current at the output end of the radio frequency path in each detection sampling period. The residual energy calculation module is used to take any detection sampling period as the current detection sampling period, use the energy dissipation variable of the current working frequency band and the detection sampling period to attenuate the residual energy characterization of the previous detection sampling period to obtain the historical residual energy, and add it to the voltage, current and instantaneous energy determined based on the current detection sampling period to obtain the residual energy characterization of the current detection sampling period. The latch parameter calculation module is used to obtain the steady-state reflection coefficient of the RF path as the latch reflection coefficient at the instant the front-end signal source is turned off. The electrothermal stress latching constant is calculated based on the initial output power of the RF path, the temperature rise characteristics of the power amplifier corresponding to the RF path, and the cumulative heat load generated by the continuous operation of the power amplifier. The switching control module is used to correct the preset basic safety energy threshold to obtain the blocking safety threshold based on the latch reflection coefficient, the electrothermal stress latch constant and the residual energy characterization of the current detection sampling cycle; When the residual energy level is not greater than the blocking safety threshold, the output control pulse drives the RF switch to switch.

2. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 1, characterized in that, The process of attenuating the residual energy characterization of the previous detection sampling period using the energy dissipation variable of the current operating frequency band and the detection sampling period to obtain the historical residual energy includes: Calculate the product of the energy dissipation variable of the current operating frequency band and the detection sampling period, and add the product to a preset constant to obtain the attenuation factor; The historical residual energy is obtained by dividing the residual energy characterization of the previous detection sampling period by the decay factor.

3. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 2, characterized in that, The acquisition of the residual energy characterization quantity of the current detection sampling period includes: Multiply the voltage, current, and sampling period of the current detection period to obtain the instantaneous energy; The instantaneous energy is added to the historical residual energy to obtain the residual energy characterization of the current detection sampling period.

4. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 1, characterized in that, The electrothermal stress latching constant is calculated based on the initial output power of the RF path, the temperature rise characteristics of the power amplifier corresponding to the RF path, and the cumulative heat load generated by the continuous operation of the power amplifier, including: The electrothermal stress latching constant is obtained by multiplying the initial output power of the radio frequency path, the temperature rise characteristics of the power amplifier corresponding to the radio frequency path, and the cumulative heat load generated by the continuous operation of the power amplifier.

5. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 4, characterized in that, The acquisition of the temperature rise characteristics of the power amplifier includes: The initial ambient temperature and the transient temperature of the pre-amplifier signal source at the moment of shutdown are obtained. The difference between the turn-off transient temperature and the initial ambient temperature is calculated, and the ratio of the difference to the initial ambient temperature is used as the temperature rise characteristic of the power amplifier.

6. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 4, characterized in that, The acquisition of the cumulative heat load generated by the continuous operation of the power amplifier includes: Obtain the total continuous operating time of the power amplifier in active state; Calculate the ratio of the total continuous working time to the preset reference time constant to obtain the time normalized value; The product of the time-normalized value and the preset frequency thermal coupling variable of the current operating frequency band is calculated, and a preset constant is added to obtain the cumulative heat load generated by the continuous operation of the power amplifier.

7. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 1, characterized in that, The blocking safety threshold is obtained by correcting the preset basic safety energy threshold based on the latch reflection coefficient, electrothermal stress latch constant, and residual energy characterization of the current detection sampling period, including: The energy normalization value is obtained by dividing the residual energy characterization value of the current detection sampling period by the reference energy constant; the stress normalization value is obtained by dividing the electrothermal stress latching constant by the reference power constant. Calculate the product of the energy normalization value and the latched reflection coefficient, and add the product to the stress normalization value and a preset constant to obtain the threshold correction factor; Divide the basic safety energy threshold corresponding to the current operating frequency band by the threshold correction factor to obtain the blocking safety threshold.

8. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 1, characterized in that, The step of outputting a control pulse to drive the RF switch switching when the residual energy level is not greater than the blocking safety threshold includes: The rate of change of residual energy is obtained based on the residual energy characterization of adjacent detection sampling periods; If the residual energy characterization of the current detection sampling period is not greater than the blocking safety threshold and the residual energy change rate is not greater than the preset convergence boundary, the output control pulse drives the radio frequency switch to switch.

9. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 8, characterized in that, The acquisition of the residual energy change rate includes: The difference between the residual energy characterization of the previous detection sampling period and the residual energy characterization of the current detection sampling period is calculated to obtain the single-step energy dissipation. Divide the single-step energy dissipation by the detection sampling period to obtain the residual energy change rate.

10. The internal switching control system of the modular radio frequency electromagnetic generator according to claim 1, characterized in that, The initialization of the residual energy characterization quantity includes: setting the initial value of the residual energy characterization quantity to 0 at the start moment when the preceding signal source is turned off.

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