Emergency power supply control system for elevator

Abstract

The application provides an elevator emergency energy storage power supply control system, comprising: a power grid three-phase mains power supply circuit, which is electrically connected with an elevator power interface, wherein a starting switch module is arranged in the power grid three-phase mains power supply circuit; an emergency power supply, which is electrically connected with the power grid three-phase mains and is used for charging the emergency power supply; an emergency power supply power supply circuit, which is electrically connected with the emergency power supply and the elevator power interface respectively; an emergency power supply switch module is arranged in the emergency power supply power supply circuit; the starting switch module and the emergency power supply switch module are electrically interlocked and are not connected at the same time. The application has a reliable electrical interlocking structure for realizing mains and emergency power supply switching, has a perfect safety interlocking mechanism, and avoids the risk of mains and emergency power supply parallel short circuit explosion.

Description

Technical Field

[0001] This invention relates to the field of elevator emergency power supply equipment technology, specifically to an elevator emergency energy storage power supply control system. Background Technology

[0002] With the acceleration of urbanization, high-rise buildings have become the core carriers of modern cities. Elevators, as an indispensable vertical transportation tool in high-rise buildings, directly affect the safety of residents' lives and property and their quality of life through their reliability and safety. Equipping high-rise elevators with emergency power supplies is a rigid requirement based on safety standards, regulatory requirements, and public welfare. However, current emergency power supplies for high-rise elevators generally suffer from the following technical deficiencies:

[0003] The switching between mains power and inverter emergency power supply lacks a reliable electrical interlock structure, and there is a risk of parallel short circuit and machine explosion due to the two three-phase 380V power supplies. The safety interlock mechanism is inadequate.

[0004] The power switching control logic is simple, and there is no standardized signal linkage for the switching sequence when the mains power fails and is restored. The switching process is prone to voltage drops and elevator shaking when stopping. It lacks a global emergency stop safety circuit and cannot meet the mandatory safety specifications for elevators.

[0005] The low-voltage energy storage boost circuit has insufficient protection, lacks hardware protection against reverse battery connection, and the power switching transistor is easily damaged due to incorrect battery wiring; the boost topology has simple drive control, poor stability of the output DC bus voltage, and large ripple.

[0006] The heat dissipation solution for power devices is simple, relying solely on fixed air cooling. When the elevator is under heavy load and running for a long time during inverter operation, the temperature rise of the IGBT and DCAC controller exceeds the standard, and there is no in-depth cooling measure.

[0007] The three-phase inverter circuit lacks complete strong and weak current isolation drive and dead zone anti-straight-through protection. The output pulse harmonic content is high, and there is no multi-stage filtering optimization. It is prone to electromagnetic interference and voltage spike damage to elevator traction equipment. The bus voltage design does not have sufficient margin, and waveform clipping distortion is prone to occur under heavy load.

[0008] The logic for recognizing the charging and discharging modes of energy storage batteries is simple. The switching between charging and discharging conditions relies on a single hardware signal linkage. The battery is protected only by a simple fuse and lacks BMS collaborative charging and discharging protection, which poses risks of cell overcharging, over-discharging, excessive voltage difference, and overheating damage.

[0009] The inverter output is not designed with reactive power compensation and zero-sequence harmonic suppression structure for elevator inductive loads, resulting in large voltage fluctuations, high operating noise, and large power loss of the whole machine when the load changes suddenly.

[0010] Given the numerous safety and performance deficiencies in existing technologies, there is an urgent need for a completely new elevator emergency energy storage power supply architecture that fully integrates dual power supply interlocking switching, push-pull voltage boosting, graded intelligent temperature control, isolated three-phase SPWM inverter, integrated battery charging and discharging management, and multiple hardware safety protection circuits to solve the safety hazards and performance shortcomings of existing products. Summary of the Invention

[0011] In order to overcome the defects existing in the prior art, the purpose of this invention is to provide an elevator emergency energy storage power supply control system.

[0012] To achieve the above-mentioned objectives of the present invention, the present invention provides an elevator emergency energy storage power supply control system, comprising:

[0013] The three-phase mains power supply circuit is electrically connected to the elevator power interface, and a start switch module is provided in the three-phase mains power supply circuit.

[0014] An emergency power supply is electrically connected to the three-phase mains power grid and is used to charge the emergency power supply.

[0015] An emergency power supply circuit is electrically connected to both the emergency power supply and the elevator power interface; an emergency power supply switch module is provided in the emergency power supply circuit.

[0016] The start switch module and the emergency power supply switch module are electrically interlocked and cannot be turned on at the same time.

[0017] Optionally, the start switch module includes:

[0018] The first relay KM1 has its coil electrically connected between the neutral and live wires of the three-phase mains power grid.

[0019] The first relay KM1 has a set of three-phase main normally open contacts, which are set in the three-phase mains power supply circuit of the power grid.

[0020] The start switch is electrically connected to the connection line between the coil of the first relay and the three-phase mains power.

[0021] The emergency power supply switch module includes:

[0022] The second relay KM2 has its coil electrically connected between the neutral and live wires of the emergency power supply.

[0023] The normally closed contact of the first relay KM1 is located on the connection line between the coil of the second relay and the emergency power supply.

[0024] The second relay KM2 has a set of three-phase main normally open contacts, which are located on the emergency power supply circuit.

[0025] Optionally, a globally normally closed emergency stop switch is also included, which is installed on the three-phase mains power supply circuit and the emergency power supply circuit of the power grid.

[0026] Optionally, the emergency power supply includes an emergency battery pack, a DC-AC module, and an AC-DC module;

[0027] The emergency battery pack integrates a matching BMS battery management and protection board.

[0028] The ACDC module is electrically connected between the emergency battery pack and the three-phase mains power, and is used to convert the three-phase mains power into DC power and store it in the emergency battery pack.

[0029] The DC-AC module is electrically connected between the emergency battery pack and the elevator power interface, and is used to convert the DC power output from the emergency battery pack into three-phase AC power to provide power to the elevator.

[0030] Optionally, the DC-AC module includes:

[0031] A boost circuit, which is electrically connected to the emergency battery pack, is used to boost the DC power supplied by the emergency battery pack.

[0032] An optocoupler isolation drive circuit, whose input terminal is connected to the SPWM pulse signal output terminal of a control module, is used for strong and weak current isolation transmission, and for power amplification of the SPWM pulse signal output by the control module.

[0033] The DC-AC circuit has its driving terminal electrically connected to the output terminal of the optocoupler-isolated driving circuit, and its voltage input terminal electrically connected to the output terminal of the boost circuit. The driving voltage output by the optocoupler-isolated driving circuit drives the DC-AC circuit to convert the output circuit of the boost circuit into a three-phase AC charging circuit. Optionally, the boost circuit includes a reverse diode, a third MOSFET, a fourth MOSFET, a high-frequency transformer, a rectifier circuit, and an energy storage filter capacitor module.

[0034] The positive output terminal of the emergency battery pack is electrically connected to the center tap of the high-frequency transformer, and the negative output terminal of the emergency battery pack is connected to the source of the third MOSFET and the fourth MOSFET via the reverse diode.

[0035] The drains of the third and fourth MOSFETs are respectively connected to the two winding taps of the high-frequency transformer; the gates of the third and fourth MOSFETs are connected to the output pin of the PWM controller chip, and the PWM controller chip outputs two complementary driving levels to control the on / off timing of the third and fourth MOSFETs, so that the third and fourth MOSFETs are alternately turned on and off.

[0036] The secondary winding of the high-frequency transformer outputs a high-frequency AC pulsating voltage, which is connected in series with the rectifier circuit at the rear end for AC-DC conversion. The output terminal of the rectifier circuit is electrically connected to the energy storage filter capacitor module, and the output terminal of the energy storage filter capacitor module is connected to the DC-AC circuit.

[0037] The boost circuit is a push-pull boost circuit. The reverse diode V2 is mainly used for reverse connection protection, isolating reverse voltage and preventing damage to the power transistor. The third MOSFET V3 and the fourth MOSFET V4 are high-frequency switching power devices, which work with the driver chip to achieve alternating chopping and generate high-frequency pulsating DC. The SG3525 PWM driver chip outputs two drive signals to the gate of the third MOSFET V3 and the fourth MOSFET V4 to control the switching timing and switching frequency. The high-frequency transformer T1 preferably, but not limited to, adopts a center-tapped push-pull topology boost transformer, with a primary-to-secondary turns ratio of 1:5 to achieve voltage ratio boost. The rectifier circuit V5 preferably, but not limited to, adopts a rectifier bridge, rectifier diodes, etc. The energy storage filter capacitor module preferably, but not limited to, consists of multiple capacitors connected in parallel.

[0038] Optionally, the optocoupler driving circuit includes a control module and six optocoupler isolation driving boards;

[0039] The control module outputs three complementary SPWM pulse signals, each of which is connected to the low-voltage primary side of the two optocoupler isolation driver boards; the secondary side of the optocoupler isolation driver board outputs a drive voltage to the drive terminal of the DC-AC circuit.

[0040] Optionally, the DC-AC circuit includes a three-phase inverter bridge, a three-phase filter, and a star-connected large-capacity capacitor.

[0041] The three-phase inverter bridge includes three half-bridge units, each half-bridge unit including upper and lower IGBT power transistors. The emitter (E) of the upper IGBT power transistor in each half-bridge unit is shorted to the collector (C) of the lower IGBT power transistor, forming the AC output node for that phase. The three AC output nodes corresponding to the three half-bridge units are electrically connected to the U, V, and W input terminals of the three-phase filter, respectively. The output terminal of the three-phase filter is connected to the star-connected large-capacity capacitor. The star-connected large-capacity capacitor rectifies and filters the output three-phase voltage, and the rectified and filtered three-phase voltage is connected to the elevator power interface.

[0042] The gate of each half-bridge unit's two IGBT power transistors is respectively connected to the drive voltage after the three complementary SPWM pulse signals are amplified by the optocoupler isolation driver board.

[0043] The collector (C) of the upper IGBT power transistor in each half-bridge unit is uniformly connected to the positive terminal of the DC bus of the boost circuit;

[0044] The emitter (E) of the lower IGBT power transistor in all half-bridge units is uniformly connected to the negative terminal of the DC bus of the boost circuit;

[0045] The emitter (E) of each IGBT power transistor is connected to the GND terminal of the corresponding optocoupler isolation driver board.

[0046] In this DC-AC circuit, the emitter (E) of the upper IGBT power transistor in each half-bridge unit is at a floating potential, with a floating voltage range of (0V - output voltage of the boost circuit). This ensures that the voltage difference between the gate (G) and emitter (E) of the upper IGBT power transistor meets the switching threshold requirements of the IGBT power transistor.

[0047] In this DC-AC circuit, the three-phase filter circuit and the star-connected large-capacity capacitor can:

[0048] Filtering out high-frequency switching harmonics and restoring standard sine waves: Six IGBT power transistors rely on high-speed switching to cut high-voltage DC into alternating high and low pulse voltages. These pulses contain a large amount of high-frequency switching noise, resulting in severe waveform distortion, making them unsuitable for direct supply to elevators. Therefore, the filter uses an inductor in series and a capacitor in parallel for each phase. The inductor obstructs the flow of high-frequency harmonics, while the capacitor discharges high-frequency glitches, allowing only a 50Hz power frequency sine wave to pass through, thus smoothing the distorted pulses into a smooth AC current.

[0049] Suppressing voltage spikes and reducing equipment insulation and interference risks: The voltage change rate of IGBT power transistors is extremely fast during turn-on and turn-off, generating instantaneous high voltage spikes; the series inductor slows down the voltage rise and fall rate, weakens the spike amplitude, avoids breakdown of elevator insulation components, and at the same time reduces high-frequency electromagnetic interference, protecting control modules, optocouplers and other weak current control circuits.

[0050] Buffering load surges and stabilizing output voltage amplitude: When elevator emergency load starts and stops or load changes suddenly, the current fluctuates dramatically; the inductor impedes the sudden current change, buffering the surge current, and the three-phase line voltage is stabilized within the standard AC380V range without significant deviation.

[0051] Blocking harmonic backflow and protecting the front-end IGBT power transistors: Without a three-phase filter circuit, load-side harmonics and inrush currents will flow back to the inverter bridge, increasing the heat loss of the IGBT power transistors during conduction and switching. The filter blocks harmonic backflow, reduces power transistor heating, and, together with the overall cooling circuit, improves the stability of continuous operation of the high-voltage inverter.

[0052] Star-connected large-capacity capacitors eliminate three-phase zero-sequence harmonics and balance three-phase voltage: Elevator loads are prone to three-phase load imbalance, generating 3rd and multiples of 3rd zero-sequence harmonics during operation; the star-connected common neutral point guides the zero-sequence harmonics, avoids harmonic accumulation and line heating, automatically balances the three-phase voltage difference, and prevents single-phase voltage from being too high or too low.

[0053] Rapid energy storage and voltage stabilization during load surges to suppress voltage drops: The capacitor has short-term energy storage capability. When the elevator load increases suddenly and the current surges, the capacitor quickly releases electrical energy to make up for the instantaneous power gap, avoids a large drop in output voltage, and ensures the accuracy of AC380V output.

[0054] Capacitors absorb residual harmonics, further optimizing waveform quality: Three-phase filter circuits cannot completely filter out minute carrier noise. Large-capacity star capacitors form a low-impedance path for high-frequency ripple, absorbing residual small-amplitude harmonics, resulting in a smoother sinusoidal waveform supplied to the elevator, reducing equipment operating noise and heat generation.

[0055] Capacitors compensate for reactive power in inductive loads, reducing overall machine losses: Elevator equipment is an inductive load, consuming reactive current during operation and increasing the input current on the DC bus side; star-connected capacitors output capacitive reactive power to offset inductive reactive power, improving the overall power factor, reducing the input current on the high-voltage DC bus, reducing IGBT conduction losses, and reducing heat generation.

[0056] Shutdown buffer to protect downstream elevator equipment: When the inverter system stops or the drive pulse is blocked, the capacitor smoothly releases the internal stored electrical energy to avoid a sudden drop in output voltage, prevent voltage surges from impacting the elevator's internal control board, and extend the load's service life.

[0057] Optionally, it also includes a temperature control unit, the temperature control unit comprising:

[0058] Temperature acquisition module for real-time temperature monitoring of emergency power supply;

[0059] Air-cooled heat dissipation module, used to cool the emergency power supply with air;

[0060] A semiconductor cooling module is installed on the emergency power supply to dissipate heat from the emergency power supply.

[0061] The control module has its input terminal electrically connected to the signal output terminal of the temperature acquisition module; the semiconductor refrigeration control signal output terminal of the control module is connected to the control terminal of the semiconductor refrigeration module, and the control module outputs a control signal according to the temperature signal to control the start and stop of the semiconductor refrigeration module.

[0062] Optionally, the temperature control unit further includes a drive unit, the output of which is connected to the power adjustment terminal of the semiconductor refrigeration module. The drive unit is used to output a drive voltage to drive the semiconductor refrigeration module to operate at the power corresponding to the drive voltage.

[0063] The power regulation control signal output terminal of the control module is electrically connected to the signal input terminal of the drive unit. The control module calculates the target power of the current semiconductor refrigeration module based on the temperature signal and the preset target temperature, and outputs a power regulation control signal to make the semiconductor refrigeration module work at the target power. The drive unit receives the power regulation control signal and outputs a drive voltage corresponding to the power regulation control signal to the semiconductor refrigeration module, so that the semiconductor refrigeration module works at the power corresponding to the drive voltage.

[0064] The beneficial effects of this invention are:

[0065] This invention features a reliable electrical interlock structure for switching between mains power and emergency power, and a comprehensive safety interlock mechanism, thus avoiding the risk of short circuit and machine explosion caused by parallel connection of mains power and emergency power.

[0066] The BMS battery management and protection board in the emergency battery pack of this invention improves the safety of the emergency power supply; the boost circuit relies on a PWM control chip, a high-frequency transformer, rectification, and multi-stage capacitor voltage regulation to achieve high-frequency chopping boost, stably outputting a high-voltage bus and providing sufficient voltage margin for the subsequent inverter; the optocoupler isolation drive circuit realizes strong and weak current isolation drive and dead-zone shoot-through protection for the DC-AC module. In the DC-AC circuit, a few microseconds of full shutdown interval are forcibly inserted when the upper and lower IGBT power transistors switch, preventing simultaneous short circuits of the upper and lower transistors on the same phase from the source.

[0067] This invention introduces the concept of semiconductor cooling. Semiconductors can play a good role in heat conduction. When the temperature rise of IGBT and DCAC modules exceeds the standard during long-term heavy-load inverter operation of elevators, semiconductor deep cooling can be used to protect the emergency power supply and prevent the power transistor components from overheating and burning out.

[0068] Additional aspects and advantages of the invention will be set forth in part in the description which follows, and in part will be obvious from the description, or may be learned by practice of the invention. Attached Figure Description

[0069] The above and / or additional aspects and advantages of the present invention will become apparent and readily understood from the description of the embodiments taken in conjunction with the following drawings, in which:

[0070] Figure 1 This is a schematic diagram of the mains power and emergency power switching logic circuit in this invention;

[0071] Figure 2 This is a schematic diagram of an emergency power supply and its power supply circuit.

[0072] Figure 3 This is a schematic diagram of a boost circuit;

[0073] Figure 4 This is a schematic diagram of an optocoupler isolation drive circuit;

[0074] Figure 5 This is a schematic diagram of a DC-AC circuit;

[0075] Figure 6 This is a schematic diagram of the temperature control unit circuit;

[0076] Figure 7 This is a schematic diagram of the auxiliary power supply;

[0077] Figure 8 This is a schematic diagram illustrating the principle of the present invention. Detailed Implementation

[0078] Embodiments of the present invention are described in detail below. Examples of these embodiments are shown in the accompanying drawings, wherein the same or similar reference numerals denote the same or similar elements or elements having the same or similar functions throughout. The embodiments described below with reference to the accompanying drawings are exemplary and are only used to explain the present invention, and should not be construed as limiting the present invention.

[0079] In the description of this invention, unless otherwise specified and limited, it should be noted that the terms "installation", "connection" and "linking" should be interpreted broadly. For example, they can refer to mechanical or electrical connections, or internal connections between two components. They can be direct connections or indirect connections through an intermediate medium. Those skilled in the art can understand the specific meaning of the above terms according to the specific circumstances.

[0080] like Figure 1-8 As shown, the present invention provides an elevator emergency energy storage power supply control system, including: a three-phase mains power supply circuit, an emergency power supply, and an emergency power supply circuit.

[0081] The system includes a three-phase mains power supply circuit electrically connected to the elevator power interface, and a start switch module installed in the three-phase mains power supply circuit. An emergency power supply is also electrically connected to the three-phase mains power supply for charging. An emergency power supply circuit is electrically connected to both the emergency power supply and the elevator power interface to supply power to the elevator. An emergency power supply switch module is installed in the emergency power supply circuit. The start switch module and the emergency power supply switch module are electrically interlocked and cannot be activated simultaneously.

[0082] In this embodiment, as Figure 1As shown, the start switch module includes a first relay KM1 and a start switch K1. The coil of the first relay KM1 is electrically connected between the neutral and live wires of the three-phase mains power supply; a set of three-phase normally open contacts of the first relay KM1 is located in the three-phase mains power supply circuit. The start switch K1 is electrically connected to the connection line between the coil of the first relay KM1 and the three-phase mains power supply.

[0083] The emergency power supply switch module includes a second relay KM2, the coil of which is electrically connected between the neutral and live wires of the emergency power supply; a normally closed contact of the first relay KM1 is located on the connection line between the coil of the second relay KM2 and the emergency power supply; and a set of three-phase main normally open contacts of the second relay KM2 are located on the emergency power supply circuit.

[0084] A globally normally closed emergency stop switch K2 is also installed on the three-phase mains power supply circuit and the emergency power supply circuit.

[0085] When the mains power supply is normal, such as Figure 1 As shown, when the three-phase mains power supply circuit is energized, the coil of the first relay KM1 is energized and engaged; the three-phase main normally open contact of the first relay KM1 closes, and the mains power L1 / L2 / L3 is transmitted to the elevator power interface - X4 through terminal - X3 and the three-phase main normally open contact of the first relay KM1, and the elevator is directly powered by the conventional power grid.

[0086] After the coil of the first relay KM1 is energized and engaged, the normally closed contact of the first relay KM1 opens simultaneously, the emergency power supply start signal is lost, and no power is supplied to the elevator.

[0087] After the coil of the first relay KM1 is energized and engaged, the normally closed contact of the first relay KM1 opens simultaneously, the coil of the second relay KM2 cannot be energized, and the three-phase main normally open contact of the second relay KM2 opens, thus physically isolating the emergency power supply from the elevator load.

[0088] Here, the second relay KM2 and the first relay KM1 form an electrical interlock structure, and only one of them can be activated at the same time, thus preventing the two power supplies from being short-circuited in parallel from the hardware level.

[0089] When the mains power fails or is interrupted, it automatically switches to the emergency power supply to discharge and provide power.

[0090] like Figure 1 As shown, when the external mains power is completely cut off, the coil of the first relay KM1 is de-energized and released; the three-phase main normally open contacts of the first relay KM1 open synchronously, completely cutting off the mains power input, and the elevator is disconnected from the power grid; the normally closed contacts of the first relay KM1 are mechanically reset to the closed state; after the normally closed contacts of the first relay KM1 close, the emergency power supply stably outputs the three-phase power required by the elevator.

[0091] After the normally closed contact of the first relay KM1 closes, the coil of the second relay KM2 is energized, and the three-phase main normally open contact of the second relay KM2 closes, transmitting the three-phase 380V power output from the emergency inverter to the elevator power interface-X4 via terminal-X31 and the three-phase main normally open contact of the second relay KM2. The elevator then switches to battery inverter emergency power supply.

[0092] Safety interlock logic supplement: The first relay KM1 and the second relay KM2 rely on the contacts of the first relay KM1 to build a pure electrical interlock. Under any operating condition, the two 380V power supplies of the mains and the inverter will not be output in parallel at the same time, completely avoiding the failure of parallel short circuit and machine explosion.

[0093] When mains power is restored, it will automatically switch back to mains power. For example... Figure 1 As shown, when the external mains power is restored, the coil of the first relay KM1 is energized and engaged again; the normally closed contact of the first relay KM1 momentarily opens, terminating the output of the three-phase AC voltage from the emergency power supply; the coil control circuit of the second relay KM2 is de-energized and released, and the normally open three-phase main contact of the second relay KM2 opens, cutting off the path from the emergency power supply to the elevator load; the normally open three-phase main contact of the first relay KM1 remains closed, the elevator resumes normal mains power supply, and the entire machine returns to charging standby mode.

[0094] When an elevator needs to be stopped urgently, regardless of whether the system is powered by mains power or emergency power, after the global normally closed emergency stop switch is disconnected, the coils of the first relay KM1 and the second relay KM2 will be de-energized simultaneously, and the power inputs of both mains power and emergency power will be cut off at the same time, and the elevator power circuit will be completely de-energized and the elevator will stop.

[0095] In this embodiment, the emergency power supply includes an emergency battery pack, a DC-AC module, and an AC-DC module; wherein,

[0096] The emergency battery pack integrates a matching BMS battery management and protection board.

[0097] The AD-DC module is electrically connected between the emergency battery pack and the three-phase mains power, and is used to convert the three-phase mains power into DC power and store it in the emergency battery pack.

[0098] The DC-AC module is electrically connected between the emergency battery pack and the elevator's power interface. It converts the DC power output from the emergency battery pack into three-phase AC power to provide power to the elevator. When the emergency battery pack stops working and does not supply power to the elevator, the AD-DC module charges the emergency battery pack. The accompanying BMS battery management and protection board operates in real time, automatically detecting and controlling battery overcharge and over-discharge states.

[0099] like Figure 2As shown, the three-phase AC input terminals U, V, and W of the AC-DC module are connected to the mains power. The DC bus voltage is stabilized and high-frequency ripple is filtered out by two electrolytic capacitors (C1, C2) connected in series, and then charged into the emergency battery pack.

[0100] The DC-AC module includes a boost circuit, an optocoupler-isolated drive circuit, and a DC-AC circuit. The boost circuit is electrically connected to the emergency battery pack and boosts the DC power supplied by the emergency battery pack. The input of the optocoupler-isolated drive circuit is connected to the SPWM pulse signal output of a control module for strong and weak current isolation transmission and power amplification of the SPWM pulse signal output by the control module. The drive terminal of the DC-AC circuit is electrically connected to the output of the optocoupler-isolated drive circuit, and its voltage input terminal is electrically connected to the output of the boost circuit. The drive voltage output by the optocoupler-isolated drive circuit drives the DC-AC circuit to convert the output of the boost circuit into three-phase AC charging.

[0101] like Figure 3 As shown, the boost circuit includes a reverse-connected diode V2, a third MOSFET V3, a fourth MOSFET V4, a high-frequency transformer T1, a rectifier circuit V5, and an energy storage filter capacitor module. The third MOSFET V3 and the fourth MOSFET V4 are N-channel high-power MOSFETs.

[0102] The positive output terminal of the emergency battery pack is electrically connected to the center tap of the high-frequency transformer, and the negative output terminal of the emergency battery pack is connected to the source (s) of the third MOSFET V3 and the fourth MOSFET V4 via the reverse diode V2.

[0103] The drains (D) of the third MOSFET V3 and the fourth MOSFET V4 are respectively connected to the taps of the windings on both sides of the high-frequency transformer T1. The gates (G) of the third MOSFET V3 and the fourth MOSFET V4 are connected to the output pin of the PWM controller chip. The PWM controller chip outputs two complementary drive levels to control the on / off timing of the third MOSFET V3 and the fourth MOSFET V4, causing the third MOSFET V3 and the fourth MOSFET V4 to alternately turn on and off. In this embodiment, the PWM controller chip is preferably, but not limited to, the SG3525 PWM driver chip.

[0104] The secondary winding of the high-frequency transformer T1 outputs a high-frequency AC pulsating voltage, which is connected in series with the rectifier circuit V5 at the rear end for AC-DC conversion, converting the AC pulsating output of the high-frequency transformer T1 into a DC pulsating voltage. The output terminal of the rectifier circuit V5 is electrically connected to the energy storage filter capacitor module, which filters out DC pulsating ripple and stabilizes the output of the high-voltage bus. The output terminal of the energy storage filter capacitor module is connected to the DC-AC circuit.

[0105] The principle of voltage boost is:

[0106] The negative terminal of the emergency battery pack supplies power to the source of the third MOSFET V3 and the fourth MOSFET V4 through the reverse diode V2. The unidirectional conduction characteristic of the reverse diode V2 can prevent the large current backflow from breaking down the third MOSFET V3 and the fourth MOSFET V4 when the positive and negative terminals of the battery are reversed, thus constructing a safe and stable power base circuit.

[0107] The SG3525 driver chip outputs two complementary phase drive signals to drive the gates of the third MOSFET V3 and the fourth MOSFET V4 respectively. The two MOSFETs alternately turn on and off at a fixed frequency to perform high-frequency chopping on the primary DC of the high-frequency transformer T1, converting the flat DC into high-frequency pulsating DC, which is then fed into the primary winding of the high-frequency transformer T1.

[0108] In this embodiment, the turns ratio of the primary winding to the secondary winding of the high-frequency transformer T1 is set to 1:5; high-frequency pulsating DC power is input to the primary winding, and the voltage is boosted through electromagnetic induction, while the high-frequency pulsating high-voltage alternating voltage is output from the secondary winding.

[0109] The high-frequency pulsating AC voltage output from the secondary winding of the high-frequency transformer T1 is converted into pulsating DC by the rectifier circuit. The voltage ripple is then filtered out and voltage fluctuations are suppressed by the downstream energy storage filter capacitor module, finally outputting a stable and smooth DC high voltage to supply the downstream DC-AC circuit.

[0110] like Figure 4 As shown, the optocoupler isolation drive circuit includes a control module and six optocoupler isolation drive boards. The control module generates and outputs three complementary SPWM pulse signals based on a built-in advanced timer, serving as the command source for the operation of the six IGBT power transistors in the DC-AC circuit. The software internally generates three sets of 50Hz sine reference waveforms, with the U, V, and W phase waveforms staggered by 120° to match the standard phase relationship of three-phase AC power. The sine waveform is compared with a high-frequency triangular carrier wave in real time to generate SPWM pulse waves with dynamically changing width. Each phase simultaneously outputs two complementary drive signals: one to control the power transistor of the upper bridge arm of the same phase in the DC-AC circuit, and the other to control the power transistor of the lower bridge arm of the same phase in the DC-AC circuit. The program has a built-in microsecond-level dead-time delay, forcibly inserting a few microseconds of full turn-off interval when switching between upper and lower transistors, thus preventing simultaneous short circuits of upper and lower transistors in the same phase from the source.

[0111] Since the control signal output by the control module is a low-voltage control signal, typically only 3.3V, it cannot directly drive the DC-AC circuit. Therefore, in this embodiment, each of the three complementary SPWM pulse signals output by the control module is connected to the low-voltage primary side of the two optocoupler isolation driver boards. The optocoupler isolation driver boards complete the strong and weak current isolation transmission and drive power amplification, completely isolating the high-voltage bus on the DC-AC circuit side from the control low-voltage circuit, preventing high voltage from damaging the main control of the control module. The secondary side of the optocoupler isolation driver board outputs the drive voltage to the drive terminal of the DC-AC circuit.

[0112] like Figure 5 As shown, the DC-AC circuit includes a three-phase inverter bridge, a three-phase filter V8, and a star-connected large-capacity capacitor C17.

[0113] The three-phase inverter bridge includes three half-bridge units. Each half-bridge unit includes two IGBT power transistors, an upper one and a lower one. The emitter (E) of the upper IGBT power transistor in each half-bridge unit is shorted to the collector (C) of the lower IGBT power transistor, forming the AC output node for that phase. The three AC output nodes corresponding to the three half-bridge units are electrically connected one-to-one to the U, V, and W input terminals of the three-phase filter V8. The output terminal of the three-phase filter V8 is connected to the star-connected large-capacity capacitor C17. The star-connected large-capacity capacitor C17 rectifies and filters the output three-phase voltage. The rectified and filtered three-phase voltage is then connected to the elevator power interface.

[0114] like Figure 5 As shown, the IGBT power transistors include the upper IGBT power transistor S1 of the U phase, the upper IGBT power transistor S2 of the V phase, and the upper IGBT power transistor S3 of the W phase, as well as the lower IGBT power transistor S4 of the U phase, the lower IGBT power transistor S5 of the V phase, and the lower IGBT power transistor S6 of the W phase.

[0115] The collectors (C) of the IGBT power transistors S1 (U phase), S2 (V phase), and S3 (W phase) are all connected to the positive terminal of the DC bus of the boost circuit, as shown in the diagram (640V). The emitters (E) of the IGBT power transistors S4 (U phase), S5 (V phase), and S6 (W phase) are all connected to the negative terminal of the DC bus of the boost circuit.

[0116] The gate (G) terminals of the upper IGBT power transistors S1, S2, and S3 of the U-phase, lower IGBT power transistors S4, S5, and S6 of the V-phase, V-phase, and W-phase respectively connect to the driving voltages amplified by the optocoupler isolation driving board of the three complementary SPWM pulse signals in the corresponding optocoupler driving circuits.

[0117] The emitter terminals of IGBT power transistors S1 (U phase), S2 (V phase), and S3 (W phase) are floating potentials at U, V, and W, respectively, with a fluctuation range between 0V and the output voltage of the boost circuit.

[0118] The emitter (E) terminals of all IGBT power transistors are connected to the GND terminal of the corresponding optocoupler isolation driver board. In this embodiment, as shown... Figure 4 , 5 As shown, the GND pin of the isolation optocoupler driver board for the IGBT power transistors S1 (U phase), S2 (V phase), and S3 (W phase) is individually connected to the emitter (E) of each IGBT power transistor. Similarly, the GND pin of the isolation optocoupler driver board for the IGBT power transistors S4 (U phase), S5 (V phase), and S6 (W phase) can also be individually connected to the emitter (E) of each IGBT power transistor. Alternatively, all three lower IGBTs can be connected to the same emitter (E).

[0119] like Figure 4 and Figure 5 As shown, the conduction condition of IGBT power transistor S1 on phase U is as follows: The control module drives the isolation optocoupler driver board 1, drives the S1-G terminal, applies a positive drive voltage, and IGBT power transistor S1 on phase U is turned on, making... Figure 5 Point U1 is directly connected to the high-voltage positive terminal of the boost circuit, and phase U outputs a high potential.

[0120] The conduction condition of IGBT power transistor S4 in phase U: The control module drives the optocoupler isolation driver board 4, which applies a positive drive to the gate of S4, turning on the IGBT power transistor S4 in phase U. Figure 5 Point U1 is directly connected to the high-voltage negative terminal of the boost circuit output, while the U-phase output is at a low potential. A strict rule for the U-phase is that the upper IGBT power transistor S1 and the lower IGBT power transistor S4 of the U-phase must never be turned on simultaneously; otherwise, a short circuit between the positive and negative terminals of the boost circuit output will cause the transistors to explode. The operating mode is a high-speed alternating switch: the upper IGBT power transistor S1 of the U-phase is turned on for a period of time, then turned off, briefly disconnecting all transistors (dead zone), and then the lower IGBT power transistor S4 of the U-phase is turned on again, repeating this cycle.

[0121] The conduction condition of IGBT power transistor S2 on phase V: The control module drives the optocoupler isolation driver board 2, drives the S2-G terminal, applies a positive drive voltage, and IGBT power transistor S2 on phase V turns on, making... Figure 5 Point V1 is directly connected to the high-voltage positive terminal of the boost circuit, and phase V outputs a high potential.

[0122] The conduction condition of IGBT power transistor S5 under phase V: The control module drives the optocoupler isolation driver board 5, which applies a positive drive voltage to the gate of S5, thus turning on the IGBT power transistor S5 under phase V. Figure 5Point V1 is directly connected to the high-voltage negative terminal of the boost circuit output, while phase V outputs a low potential.

[0123] V-phase hard rule: At the same time, the upper V-phase IGBT power transistor S2 and the lower V-phase IGBT power transistor S5 must never be turned on at the same time, otherwise the positive and negative terminals of the boost circuit will be short-circuited and the transistors will explode; the working mode is high-speed alternating switching: the upper V-phase IGBT power transistor S2 is turned on for a period of time, then turned off, briefly disconnected (dead zone), and then the lower V-phase IGBT power transistor S5 is turned on, and the cycle repeats.

[0124] The conduction condition of IGBT power transistor S3 on phase W: The control module drives the optocoupler isolation driver board 3 to drive the gate of S3, applying a positive drive voltage, thus turning on the IGBT power transistor S3 on phase W. Figure 5 Point W1 is directly connected to the high-voltage positive terminal of the boost circuit, and phase W outputs a high potential.

[0125] The conduction condition of IGBT power transistor S6 in phase W: The control module drives the optocoupler isolation driver board 6, which applies a positive drive to the gate of S6, thus turning on the IGBT power transistor S6 in phase W. Figure 5 Point W1 is directly connected to the high-voltage negative terminal of the boost circuit output, while phase W outputs a low potential.

[0126] W-phase hard rule: The upper IGBT power transistor S3 and the lower IGBT power transistor S6 of the W-phase must never be turned on at the same time, otherwise the positive and negative terminals of the boost circuit will be short-circuited and the transistors will explode; the working mode is high-speed alternating switching: the upper IGBT power transistor S3 of the W-phase is turned on for a period of time, then turned off, briefly disconnected (dead zone), and then the lower IGBT power transistor S6 of the W-phase is turned on again, and the cycle repeats.

[0127] At any given time, each phase is fixed to conduct in a two-choice configuration, resulting in a total of three IGBT power transistors conducting simultaneously across all three phases, one per phase. A dead-time is forcibly inserted during waveform switching, causing all IGBT power transistors to briefly turn off, completely eliminating the risk of short circuits caused by simultaneous conduction between transistors in the same phase. A typical conduction condition example is shown below:

[0128] Operating Condition 1: IGBT power transistor S1 on phase U is turned on, and IGBT power transistor S4 on phase U is turned off; IGBT power transistor S5 on phase V is turned on, and IGBT power transistor S2 on phase V is turned off; IGBT power transistor S6 on phase W is turned on, and IGBT power transistor S3 on phase W is turned off; Currently turned on transistors: S1, S5, S6; If the boost circuit outputs 640V high voltage, then the three-phase output is: U = 640V+, V = 640V-, W = 640V-.

[0129] Operating Condition 2: In phase U, IGBT power transistor S4 is on, and IGBT power transistor S1 in phase U is off; in phase V, IGBT power transistor S2 is on, and IGBT power transistor S5 in phase V is off; in phase W, IGBT power transistor S6 is on, and IGBT power transistor S3 in phase W is off; currently on transistors: S4, S2, S6; if the boost circuit outputs 640V high voltage, then the three-phase output is: U = 640V-, V = 640V+, W1 = 640V-.

[0130] Operating Condition 3: In phase U, IGBT power transistor S4 is on, and IGBT power transistor S1 in phase U is off; in phase V, IGBT power transistor S2 in phase V is off, and IGBT power transistor S5 in phase V is on; in phase W, IGBT power transistor S6 in phase W is off, and IGBT power transistor S3 in phase W is on; currently on transistors: S4, S5, S3; if the boost circuit outputs 640V high voltage, then the three-phase output is: U = 640V-, V = 640V-, W1 = 640V+.

[0131] Voltage regulation and modulation logic: The control module controls the conduction time of the upper IGBT power transistors in each phase; during the peak range of the sine wave, the upper IGBT power transistors (S1, S2, S3) conduct for a longer time, resulting in a higher average voltage for the corresponding phase; during the zero-crossing range of the sine wave, the lower IGBT power transistors (S4, S5, S6) conduct for a longer time, resulting in a lower average voltage for the corresponding phase; the duty cycle changes of the three phases U, V, and W are staggered by 120°; if the emergency battery pack outputs DC128V and the boost circuit outputs DC640V high voltage, then -U1, -V1, and -W1 output a series of alternating high and low DC640V instantaneous pulse voltages; the pulses are sent to the back-end three-phase filter V8 to filter out high-frequency switching glitches, and finally output a smooth and symmetrical three-phase AC380V power frequency alternating current.

[0132] Voltage parameter calculation and margin design: Currently output three-phase line voltage RMS values:

[0133] ,

[0134] Single-phase sine peak value:

[0135] ,

[0136] Three-phase line voltage peak

[0137] ,

[0138] Bus voltage redundancy

[0139] ΔU = U DC - U L1 = 640V − 537.24 = 102.6V

[0140] This embodiment uses a DC640V bus, which is 102.6V higher than the maximum instantaneous voltage of the output waveform, allowing for load voltage drop and dynamic load fluctuation margins, and will not cause sine wave clipping distortion.

[0141] DC voltage equivalent modulation ratio formula:

[0142] ,

[0143] Substitute parameters for calculation:

[0144] .

[0145] The standard linear modulation interval for engineering is 0 ≤ M ≤ 1. In this embodiment, M = 0.84, resulting in no overmodulation and minimal waveform distortion. The control module locks M = 0.84 to output an SPWM waveform, which is then driven by an optocoupler isolation driver board to alternately switch 6 IGBT power transistors on and off at high speed. When the IGBT power transistors are on, a 640V or 0V pulse is output at the midpoint. By dynamically changing the duty cycle, the average voltage of the pulse is equivalent to an AC waveform with a peak value of 537.4V.

[0146] The output voltage verification formula for IGBT power transistors is as follows: The output voltage is only a high-frequency pulse voltage, containing a large number of switching harmonics. After filtering by the three-phase filter V8 and the star-connected large-capacity capacitor C17, the standard output effective value formula is as follows:

[0147] ,

[0148] Substitute parameters M=0.84 and UDC=640V into the calculation:

[0149] .

[0150] The output line voltage is approximately 380V, which meets the power supply requirements of the elevator.

[0151] like Figure 2 As shown, the DC-AC module and the AC-DC module can be integrated into one bidirectional DC / AC controller.

[0152] In this embodiment, as Figure 6 As shown, it also includes a temperature control unit for controlling the temperature of the emergency power supply. The temperature control unit includes a temperature acquisition module, a wind-cooled heat dissipation module, a semiconductor refrigeration module, a drive unit, and the aforementioned control module.

[0153] The temperature acquisition module is used to monitor the temperature of the emergency power supply in real time. In this embodiment, the temperature acquisition module preferably uses an NTC2 thermistor, which is mounted on the heat sink of the bidirectional DCAC controller and the six IGBT power transistors to collect the surface temperature of the devices in real time.

[0154] The air-cooled heat dissipation module is used to cool the emergency power supply. In this embodiment, the air-cooled heat dissipation module uses a cooling fan M1 for air cooling.

[0155] The semiconductor cooling module is installed on the emergency power supply to provide deep cooling and heat dissipation for the emergency power supply;

[0156] The output terminal of the drive unit is connected to the power adjustment terminal of the semiconductor refrigeration module. The drive unit is used to output a drive voltage to drive the semiconductor refrigeration module to work at the power corresponding to the drive voltage.

[0157] The input terminal of the control module is electrically connected to the signal output terminal of the temperature acquisition module. Temperature changes are converted into linearly changing voltage signals, and the control module reads the current temperature of the power device in real time. The semiconductor cooling control signal output terminal of the control module is connected to the control terminal of the semiconductor cooling module. The control module outputs a control signal based on the temperature signal to control the start and stop of the semiconductor cooling module.

[0158] A cooling switch is installed on the power supply line of the semiconductor cooling module, and the control terminal of the cooling switch is connected to the corresponding control signal output terminal of the control module. For example... Figure 6 As shown, in this embodiment, the cooling switch is the third relay KM3.

[0159] like Figure 6 As shown, the power supply link for the temperature control circuit in this embodiment is as follows:

[0160] The external DC48V input is split into two independent power branches via fuse F2:

[0161] Branch 1: Direct-connected drive unit circuit, providing operating power to the semiconductor cooling module;

[0162] Branch 2: Connect to the isolated DC-DC module V9, which steps down to output DC12V to power the cooling fan M1 and the control module.

[0163] like Figure 7 As shown, the external DC48V can be obtained by converting the output voltage of the emergency battery pack through the auxiliary voltage source conversion module.

[0164] Assume that the trigger temperature for starting the semiconductor cooling module is set to 80°C, and switch logic control is used.

[0165] When the emergency power supply temperature is <80℃ (normal light load inverter operation), the NTC thermistor feedback temperature is below 80℃, the control module determines that it is in a low temperature state, and the cooling fan M1 continues to start and run; the third relay K3 remains open, the semiconductor cooling module has no power supply and completely stops working; the whole machine relies solely on the forced air cooling of the fan and natural heat dissipation to remove the slight heat generated by the IGBT and bidirectional DC / AC controller, and the cooling circuit operates with zero power consumption.

[0166] When the bidirectional DCAC controller operates at full load for an extended period, the high-frequency switching of the 6 IGBT power transistors generates significant power loss, and the bidirectional DCAC controller heats up simultaneously, causing the emergency power supply temperature to reach ≥80℃ (heavy-load, high-temperature inverter operation). The NTC thermistor's temperature reaches the 80℃ trigger threshold. Simultaneously, the control module outputs a switch control signal: driving the third relay K3 to engage, supplying DC48V power to the semiconductor cooling module, and energizing the TEC1-12703 semiconductor cooling chip in the semiconductor cooling module. Air cooling and semiconductor cooling work synchronously and collaboratively: the cooling chip rapidly absorbs and cools down the surface of the heat-generating device while the fan continuously blows away the heat from the hot end of the cooling chip and the heat sink of the power device, achieving bidirectional synchronous heat dissipation and rapidly lowering the overall power device temperature.

[0167] When the temperature drops below 80℃ and the dual heat dissipation devices continue to work, the temperature of the heat sink base decreases, and the temperature value sampled by the NTC thermistor is below 80℃; the control module simultaneously cancels the control signal of the third relay K3, the third relay K3 is disconnected, and the semiconductor cooling chip stops working; the cooling fan M1 remains on to maintain basic air cooling.

[0168] As long as the thermoelectric cooler is powered on, the cooling fan M1 will automatically turn on to prevent heat buildup at the hot end of the cooler from burning it out. This linkage is achieved through hardware circuitry and requires no additional software logic intervention.

[0169] In this embodiment, the temperature control unit further includes a drive unit, the output of which is connected to the power adjustment terminal of the semiconductor refrigeration module. The drive unit is used to output a drive voltage to drive the semiconductor refrigeration module to work at the power corresponding to the drive voltage.

[0170] The power regulation control signal output terminal of the control module is electrically connected to the signal input terminal of the drive unit. The control module calculates the target power of the current semiconductor refrigeration module based on the temperature signal and the preset target temperature, and outputs a power regulation control signal to make the semiconductor refrigeration module work at the target power. The drive unit receives the power regulation control signal and outputs a drive voltage corresponding to the power regulation control signal to the semiconductor refrigeration module, so that the semiconductor refrigeration module works at the power corresponding to the drive voltage.

[0171] In this embodiment, the control module preferably uses, but is not limited to, an STM32 series microcontroller, the semiconductor uses a bidirectional thermistor, and the three-phase filter is preferably, but is not limited to, a three-phase LC filter.

[0172] In the description of this specification, references to terms such as "one embodiment," "some embodiments," "example," "specific example," or "some examples," etc., indicate that a specific feature, structure, material, or characteristic described in connection with that embodiment or example is included in at least one embodiment or example of the invention. In this specification, the illustrative expressions of the above terms do not necessarily refer to the same embodiment or example. Furthermore, the specific features, structures, materials, or characteristics described may be combined in any suitable manner in one or more embodiments or examples.

[0173] Although embodiments of the invention have been shown and described, those skilled in the art will understand that various changes, modifications, substitutions and alterations can be made to these embodiments without departing from the principles and spirit of the invention, the scope of which is defined by the claims and their equivalents.

Claims

1. An elevator emergency energy storage power supply control system, characterized in that, include: The three-phase mains power supply circuit is electrically connected to the elevator power interface, and a start switch module is provided in the three-phase mains power supply circuit. An emergency power supply is electrically connected to the three-phase mains power grid and is used to charge the emergency power supply. An emergency power supply circuit is electrically connected to both the emergency power supply and the elevator power interface; an emergency power supply switch module is provided in the emergency power supply circuit. The start switch module and the emergency power supply switch module are electrically interlocked and cannot be turned on at the same time.

2. The elevator emergency energy storage power supply control system according to claim 1, characterized in that, The start switch module includes: The first relay KM1 has its coil electrically connected between the neutral and live wires of the three-phase mains power grid. The first relay KM1 has a set of three-phase main normally open contacts, which are set in the three-phase mains power supply circuit of the power grid. The start switch is electrically connected to the connection line between the coil of the first relay and the three-phase mains power. The emergency power supply switch module includes: The second relay KM2 has its coil electrically connected between the neutral and live wires of the emergency power supply. The normally closed contact of the first relay KM1 is located on the connection line between the coil of the second relay and the emergency power supply. The second relay KM2 has a set of three-phase main normally open contacts, which are located on the emergency power supply circuit.

3. The elevator emergency energy storage power supply control system according to claim 1, characterized in that, It also includes a globally normally closed emergency stop switch, which is installed on the three-phase mains power supply circuit and the emergency power supply circuit of the power grid.

4. The elevator emergency energy storage power supply control system according to claim 1, characterized in that, The emergency power supply includes an emergency battery pack, a DC-AC module, and an AC-DC module; The emergency battery pack integrates a matching BMS battery management and protection board. The ACDC module is electrically connected between the emergency battery pack and the three-phase mains power, and is used to convert the three-phase mains power into DC power and store it in the emergency battery pack. The DC-AC module is electrically connected between the emergency battery pack and the elevator power interface, and is used to convert the DC power output from the emergency battery pack into three-phase AC power to provide power to the elevator.

5. The elevator emergency energy storage power supply control system according to claim 4, characterized in that, The DC-AC module includes: A boost circuit, which is electrically connected to the emergency battery pack, is used to boost the DC power supplied by the emergency battery pack. An optocoupler isolation drive circuit, whose input terminal is connected to the SPWM pulse signal output terminal of a control module, is used for strong and weak current isolation transmission, and for power amplification of the SPWM pulse signal output by the control module. The DC-AC circuit has its driving terminal electrically connected to the output terminal of the optocoupler isolation driving circuit, and its voltage input terminal electrically connected to the output terminal of the boost circuit. The driving voltage output by the optocoupler isolation driving circuit drives the DC-AC circuit to convert the output circuit of the boost circuit into a three-phase AC charging circuit.

6. The elevator emergency energy storage power supply control system according to claim 5, characterized in that, The boost circuit includes a reverse diode, a third MOSFET, a fourth MOSFET, a high-frequency transformer, a rectifier circuit, and an energy storage filter capacitor module. The positive output terminal of the emergency battery pack is electrically connected to the center tap of the high-frequency transformer, and the negative output terminal of the emergency battery pack is connected to the source of the third MOSFET and the fourth MOSFET via the reverse diode. The drains of the third and fourth MOSFETs are respectively connected to the two winding taps of the high-frequency transformer; the gates of the third and fourth MOSFETs are connected to the output pin of the PWM controller chip, and the PWM controller chip outputs two complementary driving levels to control the on / off timing of the third and fourth MOSFETs, so that the third and fourth MOSFETs are alternately turned on and off. The secondary winding of the high-frequency transformer outputs a high-frequency AC pulsating voltage, which is connected in series with the rectifier circuit at the rear end for AC-DC conversion. The output terminal of the rectifier circuit is electrically connected to the energy storage filter capacitor module, and the output terminal of the energy storage filter capacitor module is connected to the DC-AC circuit.

7. The elevator emergency energy storage power supply control system according to claim 5, characterized in that, The optocoupler driving circuit includes a control module and six optocoupler isolation driving boards; The control module outputs three complementary SPWM pulse signals, each of which is connected to the low-voltage primary side of the two optocoupler isolation driver boards; the secondary side of the optocoupler isolation driver board outputs a drive voltage to the drive terminal of the DC-AC circuit.

8. The elevator emergency energy storage power supply control system according to claim 7, characterized in that, The DC-AC circuit includes a three-phase inverter bridge, a three-phase filter, and a star-connected large-capacity capacitor. The three-phase inverter bridge includes three half-bridge units, each half-bridge unit including upper and lower IGBT power transistors. The emitter (E) of the upper IGBT power transistor in each half-bridge unit is shorted to the collector (C) of the lower IGBT power transistor, forming the AC output node for that phase. The three AC output nodes corresponding to the three half-bridge units are electrically connected one-to-one to the U, V, and W input terminals of the three-phase filter. The output terminal of the three-phase filter is connected to the star-connected large-capacity capacitor. The star-connected large-capacity capacitor rectifies and filters the output three-phase voltage, and the rectified and filtered three-phase voltage is connected to the elevator power interface. The gate of each half-bridge unit's two IGBT power transistors is respectively connected to the drive voltage after the three complementary SPWM pulse signals are amplified by the optocoupler isolation driver board. The collector (C) of the upper IGBT power transistor in each half-bridge unit is uniformly connected to the positive terminal of the DC bus of the boost circuit; The emitter (E) of the lower IGBT power transistor in all half-bridge units is uniformly connected to the negative terminal of the DC bus of the boost circuit; The emitter (E) of each IGBT power transistor is connected to the GND terminal of the corresponding optocoupler isolation driver board.

9. The elevator emergency energy storage power supply control system according to claim 4, characterized in that, It also includes a temperature control unit, which includes: Temperature acquisition module for real-time temperature monitoring of emergency power supply; Air-cooled heat dissipation module, used to cool the emergency power supply with air; A semiconductor cooling module is installed on the emergency power supply to dissipate heat from the emergency power supply. The control module has its input terminal electrically connected to the signal output terminal of the temperature acquisition module; the semiconductor refrigeration control signal output terminal of the control module is connected to the control terminal of the semiconductor refrigeration module, and the control module outputs a control signal according to the temperature signal to control the start and stop of the semiconductor refrigeration module.

10. The elevator emergency energy storage power supply control system according to claim 9, characterized in that, The temperature control unit also includes a drive unit, the output of which is connected to the power adjustment terminal of the semiconductor refrigeration module. The drive unit is used to output a drive voltage to drive the semiconductor refrigeration module to work at the power corresponding to the drive voltage. The power regulation control signal output terminal of the control module is electrically connected to the signal input terminal of the drive unit. The control module calculates the target power of the current semiconductor refrigeration module based on the temperature signal and the preset target temperature, and outputs a power regulation control signal to make the semiconductor refrigeration module work at the target power. The drive unit receives the power regulation control signal and outputs a drive voltage corresponding to the power regulation control signal to the semiconductor refrigeration module, so that the semiconductor refrigeration module works at the power corresponding to the drive voltage.

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