Microsecond-level large-current laser driving circuit and driver

Abstract

The application provides a microsecond large-current laser driver circuit and driver, which is used for driving a control end of a pump source circuit and comprises a signal comparison module, a current control loop module and a switch driving module; the signal comparison module compares a pre-driving signal with a threshold signal and outputs an on-level signal or an off-level signal; the current control loop module is connected with a current loop signal; the current control loop module outputs a current adjusting signal according to a comparison result of the pre-conditioning signal and the current loop signal; the switch driving module is used for outputting a pump on signal when the on-level signal is detected and outputting a pump off signal when the off-level signal is detected. The signal comparison module is arranged to quickly output the on-level signal and the off-level signal to drive the switch driving module, to quickly control the conduction and the off of the pump source circuit, to shorten the power rising and falling time of the large-current constant-current laser driver in the single pump mode, to improve the laser control precision and reliability, and to reduce the circuit complexity and the laser pump source driving difficulty.

Description

Technical Field

[0001] This invention relates to the field of laser constant current drive technology, and in particular to a microsecond-level high-current laser drive circuit and driver. Background Technology

[0002] Currently, laser processing is widely used in industrial processing, and the dynamic response characteristics of high-power lasers have become one of the core indicators for evaluating their performance. Specifically, the output optical pulse waveform of a laser is directly controlled by the driving current waveform of its internal pump source. Therefore, the rise time and fall time of the current in the pump source driving circuit directly determine the steepness of the leading and trailing edges and the pulse width modulation accuracy of the laser output optical pulse.

[0003] Existing technologies generally employ fast drive circuits using milliampere-level low-current pump sources, leveraging the rapid switching characteristics of semiconductor switching devices under low-current conditions to achieve rapid current rise and fall. However, under high-current operating conditions of tens of amperes, maintaining constant current drive results in internal current loops causing drive delays, making microsecond-level rapid control difficult. To address this issue, a multi-pump mode is commonly used, optically coupling the pump light outputs from multiple rapidly modulated low-current pump sources to synthesize a high-power, high-energy output laser. However, using a multi-pump mode under high-current conditions results in large circuit size, high control complexity, and large drive deviations. On the other hand, a single-pump mode offers slow drive speed and low processing accuracy, limiting the applicability of lasers in high-speed scanning processing and patterned microstructure fabrication.

[0004] Therefore, existing technologies still need to be improved and developed. Summary of the Invention

[0005] In view of the shortcomings of the prior art, the purpose of this invention is to provide a microsecond-level high-current laser driving circuit and driver to solve the problem that the existing tens of ampere-level high-current laser driving circuits have low switching speed in single-pump mode constant current control, which makes it impossible to achieve microsecond-level fast control and meet the processing accuracy requirements.

[0006] The technical solution of the present invention is as follows: This invention provides a microsecond-level high-current laser driving circuit, which is used to drive the control terminal of the pump source circuit, including: A signal comparison module is provided, wherein the signal terminal of the signal comparison module is connected to a pre-drive signal, and is used to compare the pre-drive signal with a threshold signal. When the pre-drive signal is greater than the threshold signal, a start-up level signal is output, and when the pre-drive signal is less than the threshold signal, a stop-down level signal is output. The level switching time of the signal comparison module is in the sub-microsecond range. A current control loop module is provided, wherein a first input terminal of the current control loop module is connected to a pre-conditioning signal, and a second input terminal of the current control loop module is connected to the current sampling terminal of the pump source circuit for receiving a current loop signal; the current control loop module compares the pre-conditioning signal with the current loop signal and outputs a current adjustment signal based on the comparison result; A switch driver module, wherein the input terminal of the switch driver module is connected to the current control loop module and the signal comparison module, and the output terminal of the switch driver module is connected to the control terminal of the pump source circuit, for outputting a pump working signal to the control terminal of the pump source circuit according to the current adjustment signal when the start-up level signal is received, and outputting a pump turn-off signal to the control terminal of the pump source circuit when the turn-off level signal is received. The signal comparison module includes a signal comparison unit and a first switching unit; the signal comparison unit is respectively connected to a first operating voltage and the pre-drive signal, and is used to compare the magnitudes of the first operating voltage and the pre-drive signal to obtain a comparison result, and output a first switching signal according to the comparison result; The control terminal of the first switching unit is connected to the signal comparison unit and is used to receive the first switching signal; the first connection terminal of the first switching unit is connected to the common connection terminal of the switch driving module and the current control loop module, and the second connection terminal of the first switching unit is grounded and is used to turn the switch driving module on or off according to the first switching signal.

[0007] A further embodiment of the present invention includes a differential conversion module, wherein the input terminal of the differential conversion module is connected to the pre-differential signal, the first output terminal of the differential conversion module is connected to the signal comparison module, and the second output terminal of the differential conversion module is connected to the current control loop module, for outputting the pre-driving signal to the signal comparison module and the pre-conditioning signal to the current control loop module according to the pre-differential signal.

[0008] In a further embodiment of the present invention, the current control loop module includes a current loop for negative feedback control of current stabilization; the response speed of the current control loop module is slower than the switching speed of the signal comparison module. In a further embodiment of the present invention, the signal comparison module further includes a second switching unit, the control terminal of which is connected to the signal comparison unit for receiving a first switching signal; the first connection terminal of the second switching unit is connected to the first input terminal of the current control loop module, and the second connection terminal of the second switching unit is grounded, and is used to ground and disconnect the first input terminal of the current control loop module according to the first switching signal.

[0009] In a further embodiment of the present invention, the switch driving module is also connected to the second input terminal of the current control loop module. When the signal comparison module outputs the turn-off level signal, the second input terminal of the current control loop module is connected to the control terminal of the pump source circuit through the switch driving module.

[0010] In a further embodiment of the present invention, the switch driving module includes: a fifth capacitor, a sixteenth resistor, a seventeenth resistor, a first transistor, a second transistor, and a first diode; wherein, One end of the fifth capacitor and one end of the sixteenth resistor are connected to the second operating voltage, and the other end of the fifth capacitor is grounded; the other end of the sixteenth resistor is connected to the collector of the first transistor, and the bases of the first transistor and the second transistor are connected to the current control loop module; the emitters of the first transistor and the second transistor are connected, and the collector of the second transistor is connected to the second input terminal of the current control loop module; The anode of the first diode is connected to the base of the first transistor and the base of the second transistor, and the cathode of the first diode is connected to the signal comparison module; one end of the seventeenth resistor is connected to the collector of the first transistor and the collector of the second transistor, and the other end of the seventeenth resistor is connected to the control terminal of the pump source circuit.

[0011] In a further embodiment of the present invention, the current control loop module includes: a tenth resistor, an eleventh resistor, a twelfth resistor, a thirteenth resistor, a fourteenth resistor, a fifteenth resistor, a third capacitor, a fourth capacitor, and a third operational amplifier; wherein, One end of the eleventh resistor is connected to the current sampling terminal of the pump source circuit, and the other end of the eleventh resistor is connected to the inverting input terminal of the third operational amplifier; one end of the tenth resistor is connected to the signal comparison module, and the other end of the tenth resistor and one end of the twelfth resistor are connected to the non-inverting input terminal of the third operational amplifier; the other end of the twelfth resistor is connected to one end of the thirteenth resistor, and the other end of the thirteenth resistor is connected to the first operating voltage; The output terminal of the third operational amplifier is connected to one end of the fifteenth resistor, one end of the third capacitor, and one end of the fourth capacitor, respectively; the other end of the third capacitor and the other end of the fourth capacitor are connected to one end of the fourteenth resistor, and the other end of the fourteenth resistor is connected to the inverting input terminal of the third operational amplifier. The other end of the fifteenth resistor is connected to the switch drive module.

[0012] In a further embodiment of the present invention, the preamplifier differential signal includes a positive preamplifier signal and a negative preamplifier signal, and the differential conversion module includes: an eighteenth resistor, a nineteenth resistor, a twentieth resistor, a twenty-first resistor, a twenty-second resistor, a twenty-third resistor, a twenty-fourth resistor, a twenty-fifth resistor, a twenty-sixth resistor, a sixth capacitor, a seventh capacitor, an eighth capacitor, a ninth capacitor, a tenth capacitor, an eleventh capacitor, a base variable resistor, and a first operational amplifier; wherein, One end of the eighteenth resistor is connected to the positive preamplifier signal, and the other end of the eighteenth resistor is connected to one end of the nineteenth resistor, one end of the seventh capacitor, and the non-inverting input of the first operational amplifier; the other ends of the nineteenth resistor and the other end of the seventh capacitor are grounded. One end of the twentieth resistor is connected to the negative preamplifier signal and is connected to one end of the twentieth eleventh resistor and one end of the sixth capacitor, respectively. The other end of the twentieth resistor and the other end of the sixth capacitor are grounded. The other end of the twentieth resistor is connected to the inverting input terminal of the first operational amplifier, one end of the twentieth eleventh resistor, and one end of the eighth capacitor, respectively. The positive input terminal of the first operational amplifier is connected to the second operating voltage and is connected to one end of the ninth capacitor; the negative input terminal of the first operational amplifier is grounded and is connected to the other end of the ninth capacitor; the output terminal of the first operational amplifier is connected to the other end of the twenty-second resistor, the other end of the eighth capacitor, one end of the tenth capacitor, and one end of the twenty-third resistor, and is used to connect to the signal terminal of the signal comparison module. The other end of the 23rd resistor is connected to one end of the 24th resistor, one end of the 25th resistor, one end of the 26th resistor, and one end of the 11th capacitor, and is used to connect to the current control loop module; the other end of the 24th resistor is connected to the first fixed end of the base variable resistor, and the second fixed end of the base variable resistor, the movable end of the base variable resistor, the other end of the 10th capacitor, the other end of the 25th resistor, the other end of the 26th resistor, and the other end of the 11th capacitor are grounded.

[0013] In a further embodiment of the present invention, the signal comparison unit includes: a first resistor, a second resistor, a third resistor, a fourth resistor, a fifth resistor, and a second operational amplifier; wherein, One end of the first resistor is connected to the pre-drive signal, and the other end of the first resistor is connected to one end of the third resistor and the inverting input terminal of the second operational amplifier, respectively. One end of the second resistor is connected to the first operating voltage, and the other end of the second resistor is connected to one end of the fourth resistor and the non-inverting input terminal of the second operational amplifier, respectively; the other ends of the third resistor and the other ends of the fourth resistor are grounded. The output of the second operational amplifier is connected to the first switching unit; One end of the fifth resistor is connected to the common terminal of the non-inverting input of the second operational amplifier and the fourth resistor, and the other end of the fifth resistor is connected to the output of the second operational amplifier.

[0014] Based on the same inventive concept, the present invention also provides a driver, which includes the microsecond-level high-current laser driving circuit and pump source circuit described above; wherein, The switch driving module of the microsecond-level high-current laser driving circuit is connected to the control terminal of the pump source circuit and is used to output the pump working signal or the pump turning off signal to the pump source circuit. The pump source circuit is used to collect and operate according to the pump working signal or the pump turning off signal, and output a current loop signal to the current control loop module.

[0015] This invention provides a microsecond-level high-current laser driving circuit and driver. The microsecond-level high-current laser driving circuit is used to drive the control terminal of a pump source circuit, including: a signal comparison module, the signal terminal of which is connected to a pre-drive signal, used to compare the pre-drive signal with a threshold signal, and outputs a start-up level signal when the pre-drive signal is greater than the threshold signal, and outputs a turn-off level signal when the pre-drive signal is less than the threshold signal; the level switching time of the signal comparison module is sub-microsecond; a current control loop module, the first input terminal of which is connected to a pre-conditioning signal, and the second input terminal of which is connected to the current sampling terminal of the pump source circuit, used to connect to a current loop signal; the current control loop module compares the pre-conditioning signal with the current loop signal, and outputs a current adjustment signal according to the comparison result; and a switch driving module, the input terminal of which is connected to the current control loop module and the signal... The comparison module is connected, and the output terminal of the switch drive module is connected to the control terminal of the pump source circuit. It is used to output a pump operating signal to the control terminal of the pump source circuit according to the current adjustment signal when the start-up level signal is received, and to output a pump turn-off signal to the control terminal of the pump source circuit when the turn-off level signal is received. The signal comparison module includes a signal comparison unit and a first switch unit. The signal comparison unit is connected to a first operating voltage and the pre-drive signal, respectively, and is used to compare the magnitudes of the first operating voltage and the pre-drive signal to obtain a comparison result, and output a first switch signal according to the comparison result. The control terminal of the first switch unit is connected to the signal comparison unit and is used to receive the first switch signal. The first connection terminal of the first switch unit is connected to the common connection terminal of the switch drive module and the current control loop module, and the second connection terminal of the first switch unit is grounded, and is used to turn the switch drive module on or off according to the first switch signal. This invention incorporates a signal comparison module within a high-current laser driver circuit operating at tens of amperes. This allows the signal comparison module to rapidly output start-up and stop-down level signals to drive a switch driver module when the current loop in a single-pump mode causes a delay in the current control loop. The switch driver module then quickly controls the turn-on and turn-off of the pump source circuit, shortening the power rise and fall time for a high-current constant-current laser driver in single-pump mode. This improves laser control accuracy and reliability while reducing circuit complexity and the difficulty of driving the laser pump source. Attached Figure Description

[0016] To more clearly illustrate the technical solutions in the embodiments of the present invention or the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on the structures shown in these drawings without creative effort.

[0017] Figure 1 This is a schematic diagram of a microsecond-level high-current laser driving circuit in a preferred embodiment of the present invention.

[0018] Figure 2 This is a schematic diagram of a module of a microsecond-level high-current laser driving circuit in a further embodiment of a preferred embodiment of the present invention.

[0019] Figure 3 This is a circuit diagram of the microsecond-level high-current laser driving circuit in this invention.

[0020] The following labels in the attached diagram represent: 1. Pump source circuit; 100. Signal comparison module; 110. Signal comparison unit; 120. First switching unit; 130. Second switching unit; 200. Current control loop module; 300. Switch drive module; 400. Differential conversion module. Detailed Implementation

[0021] This invention provides a microsecond-level high-current laser driving circuit and driver. To make the objectives, technical solutions, and effects of this invention clearer and more explicit, the invention will be further described in detail below with reference to the accompanying drawings and examples. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.

[0022] In the implementation methods and claims, unless otherwise specified in the text, the terms "a," "an," "the," and "the" may also include plural forms. If the embodiments of the present invention involve descriptions of "first," "second," etc., such descriptions are for descriptive purposes only and should not be construed as indicating or implying their relative importance or implicitly specifying the number of indicated technical features. Therefore, a feature defined with "first" or "second" may explicitly or implicitly include at least one of those features.

[0023] It should be further understood that the term "comprising" as used in this specification means the presence of the stated features, integers, steps, operations, elements, and / or components, but does not exclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and / or groups thereof. It should be understood that when we say an element is "connected" or "coupled" to another element, it can be directly connected or coupled to the other element, or there may be intermediate elements. Furthermore, "connected" or "coupled" as used herein can include wireless connections or wireless coupling. The term "and / or" as used herein includes all or any unit and all combinations of one or more associated listed items.

[0024] It will be understood by those skilled in the art that, unless otherwise defined, all terms used herein (including technical and scientific terms) have the same meaning as commonly understood by one of ordinary skill in the art to which this invention pertains. It should also be understood that terms such as those defined in general dictionaries should be understood to have the same meaning as in the context of the prior art, and should not be interpreted in an idealized or overly formal sense unless specifically defined as herein.

[0025] Furthermore, the technical solutions of the various embodiments can be combined with each other, but only if they are feasible for those skilled in the art. If the combination of technical solutions is contradictory or cannot be implemented, it should be considered that such combination of technical solutions does not exist and is not within the scope of protection claimed by this invention.

[0026] The inventors discovered that in the field of industrial laser processing, with increasingly stringent requirements from downstream applications for processing efficiency, heat-affected zone control, and the quality of machining irregular micro-holes, the dynamic response characteristics of high-power lasers have become one of the core indicators for evaluating their performance. Specifically, the rise and fall times of the current in the pump source drive circuit directly determine the steepness of the leading and trailing edges of the laser output pulse and the pulse width modulation accuracy. To obtain a drive current with fast rise and fall times, existing technologies generally design fast drive circuits specifically for low-current pump sources. Due to the small gate charge and low parasitic capacitance charging and discharging time constant of semiconductor switching devices under low-current conditions, it is relatively easy to achieve microsecond-level fast current rise / fall processes in milliampere-level low-current pump sources. Subsequently, this technical approach combines the pump light outputs from multiple fast-modulated low-current pump sources through optical coupling methods such as spatial beam combining, polarization beam combining, or fiber beam combining to perform power superposition on the optical path, ultimately synthesizing a high-power, high-energy output laser beam to meet the needs of high-current processing scenarios. Here, "small current" refers to milliampere-level current, while "large current" refers to current in the ampere or tens of amperes range. Optionally, the standard for fast driving is that the rise and fall times of the switching signal are less than 1 μs. This method employs a multi-pump mode, resulting in complex circuitry, large drive circuit size, complex control, large deviations, and low accuracy. While existing single-pump modes using high-current pump sources have simpler circuitry, the pump source drive circuit contains a feedback control current loop to achieve constant current control, resulting in long rise and fall times during driving, making it difficult to meet the performance requirements of existing lasers and the precision machining requirements of special materials.

[0027] Therefore, to address the problems of long rise and fall times and slow response speed of drive signals in existing high-current constant current pump source drive circuits, such as... Figure 1As shown, this invention provides a microsecond-level high-current laser driving circuit for driving the control terminal of a pump source circuit 1, comprising: a signal comparison module 100, wherein the signal terminal of the signal comparison module 100 is connected to a pre-drive signal, for comparing the pre-drive signal with a threshold signal, and outputting a start-up level signal when the pre-drive signal is greater than the threshold signal, and outputting a turn-off level signal when the pre-drive signal is less than the threshold signal; and a current control loop module 200, wherein the first input terminal of the current control loop module 200 is connected to a pre-conditioning signal, and the second input terminal of the current control loop module 200 is connected to the current sampling terminal of the pump source circuit 1, for receiving current. The current control loop module 200 compares the pre-conditioning signal with the current loop signal and outputs a current adjustment signal based on the comparison result. A switch drive module 300, whose input is connected to the current control loop module 200 and the signal comparison module 100, and whose output is connected to the control terminal of the pump source circuit 1, is used to output a pump operation signal to the control terminal of the pump source circuit 1 based on the current adjustment signal when the signal comparison module 100 outputs a start-up level signal, and to output a pump shutdown signal to the control terminal of the pump source circuit 1 when the signal comparison module 100 outputs a shutdown level signal.

[0028] For ease of explanation, the high current standard in this invention is in the tens of amperes range. Therefore, taking a pump source drive circuit with a pump source operating current of 60A as an example, the standard for fast driving is that the drive circuit can drive the switch on the pump source circuit 1 to have a turn-on time and a turn-off time of less than 1μs. Specifically, the signal comparison module 100 can be implemented using any existing logic comparison circuit. The pre-drive signal it receives is a predetermined level signal, and the level of the level signal is used to characterize the target operating state of the pump source. The signal comparison module 100 adopts a high-speed comparison architecture, and its level transition time is in the sub-microsecond range, which is much faster than the response speed of the current control loop module 200, thereby realizing fast logic control of the switch drive module 300. Simultaneously, the current control loop module 200 receives a pre-conditioning signal. The pre-conditioning signal and the pre-drive signal can be signals with the same phase, amplitude, and period, or signals obtained by processing the same signal through different signal circuits. For example, the pre-conditioning signal may pass through a capacitor filter circuit or a parallel compensation capacitor, resulting in a delay between the pre-conditioning signal and the pre-drive signal. Correspondingly, the current control loop module 200 is at least connected to the current sampling terminal of the pump source circuit 1 to acquire the operating voltage of the pump source in the subsequent circuit. It performs a difference calculation between the pre-conditioning signal at the positive terminal and the current loop signal at the negative terminal, amplifies the difference, and outputs a current adjustment signal to achieve constant current control. For example, the threshold signal can be a 0.1V voltage signal. When the pre-drive signal is low, it is less than the threshold signal, and a turn-off level signal is output to the switch drive module 300. As can be seen, the current control loop module 200 includes a control loop, which is a current loop formed by negative feedback control. This current loop causes a delay in the current adjustment signal output by the current control loop module. Since the switch drive module 300 uses logic circuits, it does not have the delay caused by the current loop, and therefore triggers and outputs a turn-off level signal before the current control loop module 200. The switch drive module 300 outputs a pump turn-off signal upon receiving the turn-off level signal. Otherwise, upon receiving the start-up level signal, the switch drive module 300 outputs a pump operating signal according to the current adjustment signal. The pump turn-off signal can be a predetermined and connected level signal, thereby switching to the pump operating signal by cutting off the connection between the switch drive module 300 and the pump turn-off signal. Similarly, the pump operating signal can also be a predetermined and connected level signal, and the connection between the switch drive module 300 and the pump operating signal can be cut off by controlling the switch to switch to the pump turn-off signal. Alternatively, a gating structure can be used to select two pre-determined and connected pump operating signals and pump shut-off signals, which will not be elaborated here.The pump operating signal is used to control the operation of the pump source circuit, causing the pump source in the circuit to emit light. The pump shut-off signal is used to drive the pump source circuit to stop operating, turning off the pump source. This allows for an increase in the driving speed of the pump source by increasing the rise and fall rates of the pump operating and pump shut-off signals.

[0029] For example, the switch driving module 300 controls its own turn-on and turn-off through the start-up level signal and the turn-off level signal, respectively, thereby outputting a pump operation signal and a pump turn-off signal according to the current adjustment signal. Before the pre-drive signal jumps to a value greater than the threshold signal, the pre-drive signal is less than the threshold signal. At this time, the switch driving module 300 remains off, and the current loop terminates the closed-loop control of the circuit loop, performing open-loop operation. Correspondingly, when the pre-drive signal is greater than the threshold signal, the signal comparison module 100 outputs a start-up level signal to the switch driving module 300, and the switch driving module 300 turns on. At startup, since the current in pump source circuit 1 has not yet been established, the current loop signal has zero output. The voltage at the non-inverting terminal of the current control loop module 200 is much higher than the voltage at the inverting terminal, and the current regulation signal is at its maximum value. The pump operating signal output by the switch drive module 300 also has the highest drive voltage, causing the controlled switching element of pump source circuit 1 to turn on extremely quickly. When the switch drive module 300 is turned on, due to the open-loop control, the operating current of pump source circuit 1 rises rapidly, achieving microsecond-level rapid startup. Thus, the pump operating signal output to the control terminal of pump source circuit 1 through the switch drive module 300 meets the requirements for high-current rapid turn-on, enabling rapid driving of a microsecond-level high-current laser.

[0030] In some preferred embodiments, the switch driving module 300 is also connected to the second input terminal of the current control loop module 200. When the signal comparison module 100 outputs a turn-off level signal, the second input terminal of the current control loop module 200 is connected to the control terminal of the pump source circuit 1 through the switch driving module 300. Thus, under normal operating conditions, the second input terminal of the current control loop module 200 samples the current loop signal to achieve constant current negative feedback control; while when the signal comparison module 100 outputs a turn-off level signal, the inverting input terminal is switched to be connected to the control terminal of the pump source circuit 1 through the switch driving module 300. At this time, the inverting input terminal samples the voltage signal of the control terminal of the pump source circuit 1, realizing that the same sampling input terminal samples for both the current sampling terminal and the switch driving module 300.

[0031] Furthermore, such as Figure 2As shown, it also includes a differential conversion module 400. The input terminal of the differential conversion module 400 is connected to the pre-differential signal. The first output terminal DA1 of the differential conversion module 400 is connected to the signal comparison module 100. The second output terminal of the differential conversion module 400 is connected to the current control loop module 200. It is used to output a pre-driving signal to the signal comparison module 100 according to the pre-differential signal, and output a pre-conditioning signal to the current control loop module 200.

[0032] The pre-amplified differential signal is an analog differential voltage used to reduce common-mode noise at the input. The differential conversion module 400 determines the logic state by comparing the voltage difference between these two differential signals. After impedance transformation and level conditioning, it outputs a pre-amplified drive signal and a pre-amplified conditioning signal to the signal comparison module 100 and the current control loop module 200, respectively, with the two signals changing synchronously. The pre-amplified drive signal is output to the signal comparison module 100 as the basis for switch logic determination. The pre-amplified conditioning signal is output to the first input terminal of the current control loop module 200 as the reference for constant current control. Thus, by providing signals to both branches simultaneously through a single differential input, the synchronous nature of the switch action and the current setting is ensured.

[0033] Furthermore, please refer to the following: Figures 2 to 3The preamplifier differential signal includes a positive preamplifier signal and a negative preamplifier signal. The differential conversion module 400 includes: an eighteenth resistor R18, a nineteenth resistor R19, a twentieth resistor R20, a twenty-first resistor R21, a twenty-second resistor R22, a twenty-third resistor R23, a twenty-fourth resistor R24, a twenty-fifth resistor R25, a twenty-sixth resistor R26, a sixth capacitor C6, a seventh capacitor C7, an eighth capacitor C8, a ninth capacitor C9, a tenth capacitor C10, an eleventh capacitor C11, a base variable resistor RW1, and a first operational amplifier U1; wherein, one end of the eighteenth resistor R18 is connected to the positive preamplifier signal. The signal is transmitted through a circuit. The other end of the eighteenth resistor R18 is connected to one end of the nineteenth resistor R19, one end of the seventh capacitor C7, and the non-inverting input of the first operational amplifier U1. The other ends of the nineteenth resistor R19 and the seventh capacitor C7 are grounded. One end of the twentieth resistor R20 is connected to a negative preamplifier signal and is connected to one end of the twenty-first resistor R21 and one end of the sixth capacitor C6. The other ends of the twenty-first resistor R21 and the sixth capacitor C6 are grounded. The other end of the twentieth resistor R20 is connected to the inverting input of the first operational amplifier U1. The input terminal, one end of the twenty-second resistor R22, and one end of the eighth capacitor C8 are connected; the positive input terminal of the first operational amplifier U1 is connected to the second operating voltage and is connected to one end of the ninth capacitor C9; the negative input terminal of the first operational amplifier U1 is grounded and connected to the other end of the ninth capacitor C9; the output terminal of the first operational amplifier U1 is connected to the other end of the twenty-second resistor R22, the other end of the eighth capacitor C8, one end of the tenth capacitor C10, and one end of the twenty-third resistor R23, and is used to connect to the signal terminal of the signal comparison module 100; the twenty-third resistor R22... The other end of resistor R23 is connected to one end of the 24th resistor R24, one end of the 25th resistor R25, one end of the 26th resistor R26, and one end of the 11th capacitor C11, respectively, and is used to connect to the current control loop module 200; the other end of the 24th resistor R24 ​​is connected to the first fixed end of the base variable resistor RW1, and the second fixed end of the base variable resistor RW1, the movable end of the base variable resistor RW1, the other end of the 10th capacitor C10, the other end of the 25th resistor R25, the other end of the 26th resistor R26, and the other end of the 11th capacitor C11 are grounded.

[0034] Optionally, the second operating voltage is 8.1V. The positive and negative preamplifier signals form a differential input pair, which are fed into the non-inverting and inverting input terminals of the first operational amplifier U1 via the eighteenth resistor R18 and the twentieth resistor R20, respectively. The eighteenth resistor R18, the nineteenth resistor R19, and the seventh capacitor C7 together form a filter network for the non-inverting input terminal, and the twentieth resistor R20, the twenty-first resistor R21, and the sixth capacitor C6 together form a filter network for the inverting input terminal, respectively, to filter out high-frequency common-mode noise and differential-mode interference at the non-inverting and inverting input terminals. The first operational amplifier U1, the twenty-second resistor R22, and the eighth capacitor C8 together form a differential amplifier circuit, which amplifies the differential voltage between the positive and negative preamplifier signals to obtain the preamplifier drive signal. At the same time, the preamplifier drive signal is output to the current control loop module 200 via the twenty-third resistor R23 as a preamplifier conditioning signal. The 23rd resistor R23, together with the 24th resistor R24, the base variable resistor RW1, the 25th resistor R25, and the 26th resistor R26, constitute a voltage divider regulation network. The 24th resistor R24, the 25th resistor R25, the 26th resistor R26, the 10th capacitor C10, and the 11th capacitor C11 form a multi-parallel lower voltage divider branch, which is used to divide and filter the pre-conditioning signal to smooth the signal waveform, suppress switching noise, and ensure that the signal sent to the subsequent stage is stable and reliable.

[0035] In some preferred embodiments, the signal comparison module 100 includes a signal comparison unit 110 and a first switching unit 120. The signal comparison unit 110 is connected to a first operating voltage and the pre-drive signal, respectively, and is used to compare the magnitudes of the first operating voltage and the pre-drive signal to obtain a comparison result, and output a first switching signal according to the comparison result. The control terminal of the first switching unit 120 is connected to the signal comparison unit 110 and is used to receive the first switching signal. The first connection terminal of the first switching unit 120 is connected to the common connection terminal of the switch driving module 300 and the current control loop module 200, and the second connection terminal of the first switching unit 120 is grounded and is used to ground and disconnect the switch driving module 300 according to the first switching signal.

[0036] The first operating voltage is a predetermined reference threshold level, optionally 5V. The signal comparison unit 110 compares the first operating voltage with the pre-drive signal in real time to obtain a comparison result, and outputs a corresponding first switch signal to the control terminal of the first switch unit 120 based on the comparison result. The signal comparison unit 110 uses a logic signal comparison circuit with an input-to-output transmission delay of microseconds or sub-microseconds, which is equivalent to rapidly flipping and outputting the first switch signal the instant the pre-drive signal crosses the threshold, meeting the requirement of fast response speed. The first switch unit 120, as a controlled switch device, receives the first switch signal and switches between on and off according to the level state of the first switch signal, thereby controlling the connection and disconnection between the common terminal and ground.

[0037] When the pre-drive signal is less than the first operating voltage, the first switch signal output by the signal comparison unit 110 is at a valid on level, and the first switch unit 120 is turned on. At this time, the common terminal of the switch drive module 300 and the current control loop module 200 is grounded through the first switch unit 120, and the input terminal of the switch drive module 300 is pulled low to ground, thereby outputting a low-level pump turn-off signal, and the pump source circuit 1 is in a turned-off state. At this time, the positive input terminal of the current control loop module 200 does not have a valid pre-conditioning signal input and is clamped to a high level. Therefore, no matter how the current loop signal fluctuates, the current control loop module 200 outputs a high-level current regulation signal, stopping the current closed-loop regulation. At the same time, the output terminal is also connected to the common terminal, and its output is clamped to ground by the first switch unit 120. The output current regulation signal is directly pulled to ground, the switch drive module 300 continuously receives a low level, and the current control loop module 200 does not participate in the drive control for the time being.

[0038] As the voltage value of the preceding drive signal gradually increases until it exceeds the first operating voltage, the comparison result of the signal comparison unit 110 flips, and the output first switch signal switches to the stop level. The first switch unit 120 quickly switches from the on state to the off state. The common terminal of the switch drive module 300 and the current control loop module 200 is no longer grounded. The current adjustment signal output by the current control loop module 200 can normally act on the common terminal and be transmitted to the switch drive module 300. Driven by the current adjustment signal, the switch drive module 300 outputs a pump operating signal. Since the current loop in the current control loop module 200 remains open-loop when the preceding drive signal is less than the first operating voltage, the operating current of the pump source circuit 1 has not yet been established at the instant the first switch unit 120 is turned off. The current loop signal is zero, and it is not affected by the loop at this time. The current rises rapidly, causing the controlled switching element of the pump source circuit 1 to turn on extremely quickly, achieving microsecond-level rapid start-up.

[0039] In some preferred embodiments, the signal comparison unit 110 includes: a first resistor R1, a second resistor R2, a third resistor R3, a fourth resistor R4, a fifth resistor R5, and a second operational amplifier U2; wherein, one end of the first resistor R1 is connected to a pre-drive signal, and the other end of the first resistor R1 is connected to one end of the third resistor R3 and the inverting input terminal of the second operational amplifier U2; one end of the second resistor R2 is connected to a first operating voltage, and the other end of the second resistor R2 is connected to one end of the fourth resistor R4 and the non-inverting input terminal of the second operational amplifier U2; the other ends of the third resistor R3 and the fourth resistor R4 are grounded; the output terminal of the second operational amplifier U2 is connected to the first switching unit 120; one end of the fifth resistor R5 is connected to the common terminal of the non-inverting input terminal of the second operational amplifier U2 and the fourth resistor R4, and the other end of the fifth resistor R5 is connected to the output terminal of the second operational amplifier U2.

[0040] Specifically, the pre-drive signal is divided by the first resistor R1 and the third resistor R3 and then fed into the inverting input of the second operational amplifier U2. The first operating voltage is divided by the second resistor R2 and the fourth resistor R4 and then input to the non-inverting input of the second operational amplifier U2 to provide a reference threshold voltage for the comparator. The reference threshold voltage is obtained from the input first operating voltage.

[0041] Meanwhile, the first switching unit 120 includes: a sixth resistor R6, a seventh resistor R7, a first capacitor C1, and a first switching transistor Q1. The sixth resistor R6 is connected to the common terminal of the output terminal of the second operational amplifier U2 and the fifth resistor R5. The other end of the sixth resistor R6 is connected to one end of the seventh resistor R7, one end of the first capacitor C1, and the gate of the first switching transistor Q1. The drain of the first switching transistor Q1 is connected to the common terminal of the switch driving module 300 and the current control loop module 200. The source of the first switching transistor Q1, the other end of the seventh resistor R7, and the other end of the first capacitor C1 are grounded.

[0042] In a further embodiment of a preferred embodiment of the present invention, the signal comparison module 100 further includes a second switching unit 130. The control terminal of the second switching unit 130 is connected to the signal comparison unit 110 and is used to receive a first switching signal. The first connection terminal of the second switching unit 130 is connected to the first input terminal of the current control loop module 200, and the second connection terminal of the second switching unit 130 is grounded and used to turn the first input terminal of the current control loop module 200 on or off according to the first switching signal.

[0043] The first input terminal of the current control loop module 200 is connected to the signal comparison module 100. The signal comparison module 100 can be connected to the current control loop module 200 via the second switching unit 130, and is used to clamp or disconnect the first input terminal of the current control loop module 200 directly to ground according to the pre-drive signal. This ensures that when the pre-drive signal is less than the threshold signal, the input signal at the first input terminal of the current control loop module 200 is at a low level, completely turning off the current control loop module 200 and improving the turn-off reliability of the laser drive circuit. The circuit structure of the second switching unit 130 can be the same as or different from that of the first switching unit 120. It is used to control the operating state of the current control loop module 200 according to the first switching signal. It can have the same internal connection relationship as the first switching unit 120, and accordingly includes: an eighth resistor R8, a ninth resistor R9, a second capacitor C2, and a third switch Q3. The eighth resistor R8 is connected to the common terminal of the output terminal of the second operational amplifier U2 and the fifth resistor R5. The other end of the eighth resistor R8 is connected to one end of the ninth resistor R9, one end of the second capacitor C2 and the gate of the third switch Q3. The drain of the third switch Q3 is connected to the first input terminal of the current control loop module 200. The source of the third switch Q3, the other end of the ninth resistor R9 and the other end of the second capacitor C2 are grounded.

[0044] In a further embodiment of the present invention, the switch driving module 300 includes: a fifth capacitor C5, a sixteenth resistor R16, a seventeenth resistor R17, a first transistor Q21, a second transistor Q22, and a first diode D1; wherein, one end of the fifth capacitor C5 and one end of the sixteenth resistor R16 are connected to a second operating voltage, and the other end of the fifth capacitor C5 is grounded; the other end of the sixteenth resistor R16 is connected to the collector of the first transistor Q21, and the bases of the first transistor Q21 and the second transistor Q22 are connected to the current control loop module 200; the first transistor... The emitter of transistor Q21 is connected to the emitter of the second transistor Q22, and the collector of the second transistor Q22 is connected to the second input terminal of the current control loop module 200; the anode of the first diode D1 is connected to the base of the first transistor Q21 and the base of the second transistor Q22, and the cathode of the first diode D1 is connected to the signal comparison module 100; one end of the seventeenth resistor R17 is connected to the collector of the first transistor Q21 and the collector of the second transistor Q22, and the other end of the seventeenth resistor R17 is connected to the control terminal of the pump source circuit 1.

[0045] Specifically, when the signal comparison module 100 outputs a turn-off level signal, the cathode potential of the first diode D1 rapidly decreases, causing the first diode D1 to forward bias and conduct. The bases of the first transistor Q21 and the second transistor Q22 are rapidly pulled low to ground. At this time, the first transistor Q21 turns off, and the second transistor Q22 turns on. Simultaneously, the common terminal of the switch drive module 300 and the current control loop module 200 is directly grounded and discharged through the low-resistance path of the diode. Therefore, the pump source circuit 1 is not connected to a signal for turn-off, significantly shortening the turn-off speed.

[0046] When the signal comparison module 100 switches from a turn-off level signal to a turn-on level signal, the first diode D1 is reverse-biased and cut off. The current adjustment signal output by the current control loop module 200 is applied to the gates of the first transistor Q21 and the second transistor Q22. Since current feedback has not yet been established at the second input terminal of the current control loop module 200 at the moment of turn-on, the current adjustment signal is at its maximum value. The second transistor Q22 is turned off, and the first transistor Q21 is turned on in a near-saturation manner. The second operating voltage provides the maximum drive current to the control terminal of the pump source circuit 1 through the sixteenth resistor R16, the first transistor Q21, and the seventeenth resistor R17, causing the voltage at the control terminal to rise rapidly, and the pump source circuit 1 to turn on quickly. Subsequently, the current loop signal is gradually established, the current control loop module 200 enters the negative feedback adjustment state, the two transistors return to the linear amplification region, and the drive current changes dynamically with the loop adjustment, eventually stabilizing the operating current of the pump source circuit 1 at the set value.

[0047] Furthermore, in this invention, the current control loop module 200 internally includes a current negative feedback closed-loop system, i.e., a current loop, used to stabilize the current through the negative feedback of the operational amplifier. When the current exceeds the current corresponding to the given current of the pre-drive signal, the output voltage of the third operational amplifier U3 is adjusted through negative feedback, i.e., the drive voltage of the second switch Q2 is changed, and the current stability is controlled by modulating the drain-source impedance of the second switch Q2. A compensation mechanism ensures that the loop has sufficient phase margin to prevent high-frequency self-oscillation. Because there is a current loop in the current control loop module 200, the response speed of the current control loop module 200 is significantly slower than the microsecond / submicrosecond switching speed of the signal comparison module 100. Therefore, at the moment of startup, the switch drive module 300 first quickly turns on the pump source circuit 1 with the highest drive voltage, and then the current control loop module 200 is turned on to perform constant current regulation.

[0048] Specifically, after the switch drive module 300 outputs a pump operating signal based on the current adjustment signal, and the pump source circuit 1 starts working, as the operating current of the pump source circuit 1 increases, the voltage value of the current loop signal acquired by the current sampling terminal gradually increases. The voltage at the inverting terminal of the current control loop module 200 increases accordingly, the difference between the positive and negative terminals decreases, the voltage value of the current adjustment signal gradually decreases, and the driving strength of the pump operating signal output by the switch drive module 300 weakens accordingly, slowing down the rate of increase of the operating current of the pump source circuit 1. Finally, when the voltage value of the current loop signal is approximately equal to the voltage value of the pre-conditioning signal, the current control loop module 200 reaches dynamic equilibrium and outputs a stable current adjustment signal. The switch drive module 300 outputs a stable pump operating signal, and the operating current of the pump source circuit 1 stabilizes at the target value set by the pre-conditioning signal, achieving high-precision constant current drive and forming a current loop that performs current feedback adjustment based on the pump source circuit 1. When pump source circuit 1 needs to be turned off, the voltage value of the pre-amplifier differential signal decreases, and the pre-amplifier drive signal output by the differential conversion module 400 decreases accordingly. When the voltage value of the pre-amplifier drive signal is lower than the threshold signal, the signal comparison module 100 quickly flips and outputs a turn-off level signal. Under the action of the turn-off level signal, the switch drive module 300 is quickly pulled low and outputs a pump turn-off signal, which causes the controlled switching element of pump source circuit 1 to turn off quickly, and the operating current of pump source circuit 1 drops rapidly to zero, achieving microsecond-level fast turn-off.

[0049] In some preferred embodiments, the current control loop module 200 includes: a tenth resistor R10, an eleventh resistor R11, a twelfth resistor R12, a thirteenth resistor R13, a fourteenth resistor R14, a fifteenth resistor R15, a third capacitor C3, a fourth capacitor C4, and a third operational amplifier U3; wherein, one end of the eleventh resistor R11 is connected to the current sampling terminal of the pump source circuit 1, and the other end of the eleventh resistor R11 is connected to the inverting input terminal of the third operational amplifier U3; one end of the tenth resistor R10 is connected to the signal comparison module 100, and the other end of the tenth resistor R10 and one end of the twelfth resistor R12 are connected to the third operational amplifier U3. The non-inverting input of the third operational amplifier U3 is connected to the first operating voltage. The other end of the twelfth resistor R12 is connected to one end of the thirteenth resistor R13. The other end of the thirteenth resistor R13 is connected to the first operating voltage. The output of the third operational amplifier U3 is connected to one end of the fifteenth resistor R15, one end of the third capacitor C3, and one end of the fourth capacitor C4. The other ends of the third capacitor C3 and the fourth capacitor C4 are connected to one end of the fourteenth resistor R14. The other end of the fourteenth resistor R14 is connected to the inverting input of the third operational amplifier U3. The other end of the fifteenth resistor R15 is connected to the switch driver module 300.

[0050] The current loop is the control loop of the linear operational amplifier. When the current rises, the voltage sampled by the sampling resistor in the pump source circuit 1 is fed back to the third operational amplifier U3 to achieve constant current output during the stable phase after the current rises. The eleventh resistor R11 is connected in series between the inverting input and the current sampling terminal of the pump source circuit 1, and together with the fourteenth resistor R14, determines the closed-loop proportional gain of the amplifier. The third capacitor C3 and the fourth capacitor C4 are connected in parallel, forming a feedback compensation network together with the fourteenth resistor R14. When the signal comparison module 100 outputs a turn-off level signal, the common terminal of the fifteenth resistor R15 and the switch drive module 300 is pulled low. Simultaneously, the potential at the non-inverting input of the third operational amplifier U3 is pulled high through the first operating voltage connected by the twelfth resistor R12 and the thirteenth resistor R13. At this time, the current loop signal at the inverting input terminal is also zero or extremely low, much lower than the potential at the non-inverting input terminal of the third operational amplifier U3. Therefore, although the output of the current control loop module 200 is pulled low by the signal comparison module 100, the switch drive module 300 receives a low-level drive signal, and the pump source circuit 1 remains off, the current control loop module 200 itself is in an open-loop state and operates. Furthermore, when a pre-drive signal greater than the threshold signal exists, the signal comparison module 100 is no longer grounded. At this time, due to the rapid rise of the logic voltage, the drive voltage in the pump source circuit 1 will be quickly established. Optionally, the pump source circuit 1 includes at least a second switch Q2 for current control and a pump source LED1, where the second switch Q2 is a power MOSFET. At this time, the second switch Q2 quickly turns on, and because it is not affected by the loop, the current rises rapidly, the current flowing through the pump source rises rapidly, and the laser driver's optical power rises faster.

[0051] Optionally, the pump source circuit 1 further includes a 27th resistor R27, a 28th resistor R28, a 29th resistor R29, a 30th resistor R30, and a 31st resistor R31 for voltage division and current sampling. The anode of the pump source LED1 is connected to the pump power supply, the cathode of the pump source LED1 is connected to the drain of the second switching transistor Q2, and the gate of the second switching transistor Q2 is connected to the output terminal of the current control loop module 200. The 27th resistor R27 is connected between the gate and source of the second switching transistor Q2. The 28th resistor R28, the 29th resistor R29, the 30th resistor R30, and the 31st resistor R31 are connected in parallel between the source of the second switching transistor Q2 and ground. The second input terminal of the current control loop module 200 is connected to the common terminal of the 28th resistor R28, the 29th resistor R29, the 30th resistor R30, and the 31st resistor R31 and the source of the second switching transistor Q2.

[0052] Specifically, the key to achieving microsecond-level high-current drive on the pump source directly controlled in this invention lies in utilizing the fact that the response speed of the logic circuit of the signal comparison module 100 when inputting the pre-drive signal is faster than the response speed of the current loop, causing the current loop to open instantly upon power-up, controlling the second switch Q2 to turn on quickly, thus achieving a rapid current increase. Furthermore, utilizing the fact that the logic circuit of the signal comparison module 100 reacts faster than the control loop when the pre-drive signal is turned off, achieving a rapid current decrease. Specifically, the delay of the signal comparison module 100 when the drive signal input level decreases is less than that of the current control loop module 200, achieving rapid drive. When the pre-drive signal is lower than the threshold signal voltage, the logic circuit output of the signal comparison module 100 quickly flips to a high-level start-up signal, driving the first switch Q1 to conduct. After the first switch Q1 conducts, it can control the second transistor Q22 to conduct quickly, while simultaneously pulling down the drive voltage in the pump source circuit 1 instantaneously. After the drive voltage is pulled low and released, the second switch Q2 is quickly turned off, the pump source current is quickly turned off, and the current drop time is extremely fast. Similarly, when the pre-drive signal is higher than the threshold signal voltage, the logic circuit output in the signal comparison module 100 quickly flips to a low level, and the totem pole circuit composed of the first transistor Q21 and the second transistor Q22 quickly turns on. Since the first working voltage connected by the twelfth resistor R12 and the thirteenth resistor R13 serves as the reference voltage, the second operational amplifier U2 is always in an open-loop state when there is no pre-drive signal. Therefore, when there is a pre-drive signal, due to the fast logic voltage speed, the first switch Q1 will be turned off in advance, so the drive voltage of the gate of the second switch Q2 will be quickly established and quickly turned on. At this time, the control terminal input of the pump source circuit 1 is not affected by the current loop. At the moment when the first switch Q1 is turned off, the second switch Q2 has the highest drive voltage and the second switch Q2 is fully turned on. At this moment, the impedance of the second switch Q2 becomes smaller, the current in the second switch Q2 rises quickly, the current flowing through the pump source rises quickly, and the laser driver optical power speed is also fast. Therefore, by modifying the circuit as described above, the rise and fall times of the laser power can meet the requirements of high-power ultrafast lasers.

[0053] Based on the same inventive concept, the present invention also provides a driver, such as... Figure 3 As shown, it includes the aforementioned microsecond-level high-current laser driving circuit and pump source circuit 1; wherein, the switch driving module 300 of the microsecond-level high-current laser driving circuit is connected to the control terminal of the pump source circuit 1, and is used to output the pump operating signal or the pump off signal to the pump source circuit 1; the pump source circuit is used to collect and operate according to the pump operating signal or the pump off signal, and output a current loop signal to the current control loop module 200. The specific implementation is as described in the embodiment of the microsecond-level high-current laser driving circuit, and will not be repeated here.

[0054] This invention provides a microsecond-level high-current laser driving circuit and driver. The microsecond-level high-current laser driving circuit is used to drive the control terminal of the pump source circuit. Its advantages are as follows: by setting a signal comparison module in the tens of amperes-level high-current laser driving circuit, when the current loop of the single-pump mode constant current drive causes a delay in the current control loop module, the signal comparison module can quickly output start-up and turn-off level signals to drive the switch driving module. This allows the switch driving module to quickly control the conduction and turn-off of the pump source circuit, shortening the power rise and fall time of the high-current constant current laser driver in single-pump mode. This improves laser control accuracy and reliability while reducing circuit complexity and the difficulty of driving the laser pump source. The laser pump source driving circuit is small in size, simple to control, highly accurate, and highly reliable.

[0055] It should be understood that the application of the present invention is not limited to the examples above. Those skilled in the art can make improvements or modifications based on the above description, and all such improvements and modifications should fall within the protection scope of the appended claims.

Claims

1. A microsecond-level high-current laser driving circuit, characterized in that, The microsecond-level high-current laser driving circuit is used to drive the control terminal of the pump source circuit, including: A signal comparison module is provided, wherein the signal terminal of the signal comparison module is connected to a pre-drive signal, and is used to compare the pre-drive signal with a threshold signal. When the pre-drive signal is greater than the threshold signal, a start-up level signal is output, and when the pre-drive signal is less than the threshold signal, a stop-down level signal is output. The level switching time of the signal comparison module is in the sub-microsecond range. A current control loop module is provided, wherein a first input terminal of the current control loop module is connected to a pre-conditioning signal, and a second input terminal of the current control loop module is connected to the current sampling terminal of the pump source circuit for receiving a current loop signal; the current control loop module compares the pre-conditioning signal with the current loop signal and outputs a current adjustment signal based on the comparison result; A switch driver module, wherein the input terminal of the switch driver module is connected to the current control loop module and the signal comparison module, and the output terminal of the switch driver module is connected to the control terminal of the pump source circuit, for outputting a pump working signal to the control terminal of the pump source circuit according to the current adjustment signal when the start-up level signal is received, and outputting a pump turn-off signal to the control terminal of the pump source circuit when the turn-off level signal is received. The signal comparison module includes a signal comparison unit and a first switching unit; the signal comparison unit is respectively connected to a first operating voltage and the pre-drive signal, and is used to compare the magnitudes of the first operating voltage and the pre-drive signal to obtain a comparison result, and output a first switching signal according to the comparison result; The control terminal of the first switching unit is connected to the signal comparison unit and is used to receive the first switching signal; the first connection terminal of the first switching unit is connected to the common connection terminal of the switch driving module and the current control loop module, and the second connection terminal of the first switching unit is grounded and is used to turn the switch driving module on or off according to the first switching signal.

2. The microsecond-level high-current laser driving circuit according to claim 1, characterized in that, It also includes a differential conversion module, the input of which is connected to the pre-differential signal, the first output of which is connected to the signal comparison module, and the second output of which is connected to the current control loop module. It is used to output the pre-driving signal to the signal comparison module and the pre-conditioning signal to the current control loop module according to the pre-differential signal.

3. The microsecond-level high-current laser driving circuit according to claim 1, characterized in that, The current control loop module contains a current loop for negative feedback control to stabilize the current; the response speed of the current control loop module is slower than the switching speed of the signal comparison module.

4. The microsecond-level high-current laser driving circuit according to claim 1, characterized in that, The signal comparison module further includes a second switching unit. The control terminal of the second switching unit is connected to the signal comparison unit and is used to receive the first switching signal. The first connection terminal of the second switching unit is connected to the first input terminal of the current control loop module. The second connection terminal of the second switching unit is grounded and is used to turn the first input terminal of the current control loop module on or off according to the first switching signal.

5. The microsecond-level high-current laser driving circuit according to claim 1, characterized in that, The switch driving module is also connected to the second input terminal of the current control loop module. When the signal comparison module outputs the turn-off level signal, the second input terminal of the current control loop module is connected to the control terminal of the pump source circuit through the switch driving module.

6. The microsecond-level high-current laser driving circuit according to claim 1, characterized in that, The switch driving module includes: a fifth capacitor, a sixteenth resistor, a seventeenth resistor, a first transistor, a second transistor, and a first diode; wherein, One end of the fifth capacitor and one end of the sixteenth resistor are connected to the second operating voltage, and the other end of the fifth capacitor is grounded; the other end of the sixteenth resistor is connected to the collector of the first transistor, and the bases of the first transistor and the second transistor are connected to the current control loop module; the emitters of the first transistor and the second transistor are connected, and the collector of the second transistor is connected to the second input terminal of the current control loop module; The anode of the first diode is connected to the base of the first transistor and the base of the second transistor, and the cathode of the first diode is connected to the signal comparison module; one end of the seventeenth resistor is connected to the collector of the first transistor and the collector of the second transistor, and the other end of the seventeenth resistor is connected to the control terminal of the pump source circuit.

7. The microsecond-level high-current laser driving circuit according to claim 1, characterized in that, The current control loop module includes: a tenth resistor, an eleventh resistor, a twelfth resistor, a thirteenth resistor, a fourteenth resistor, a fifteenth resistor, a third capacitor, a fourth capacitor, and a third operational amplifier; wherein, One end of the eleventh resistor is connected to the current sampling terminal of the pump source circuit, and the other end of the eleventh resistor is connected to the inverting input terminal of the third operational amplifier; one end of the tenth resistor is connected to the signal comparison module, and the other end of the tenth resistor and one end of the twelfth resistor are connected to the non-inverting input terminal of the third operational amplifier; the other end of the twelfth resistor is connected to one end of the thirteenth resistor, and the other end of the thirteenth resistor is connected to the first operating voltage; The output terminal of the third operational amplifier is connected to one end of the fifteenth resistor, one end of the third capacitor, and one end of the fourth capacitor, respectively; the other end of the third capacitor and the other end of the fourth capacitor are connected to one end of the fourteenth resistor, and the other end of the fourteenth resistor is connected to the inverting input terminal of the third operational amplifier. The other end of the fifteenth resistor is connected to the switch drive module.

8. The microsecond-level high-current laser driving circuit according to claim 2, characterized in that, The preamplifier differential signal includes a positive preamplifier signal and a negative preamplifier signal. The differential conversion module includes: an eighteenth resistor, a nineteenth resistor, a twentieth resistor, a twenty-first resistor, a twenty-second resistor, a twenty-third resistor, a twenty-fourth resistor, a twenty-fifth resistor, a twenty-sixth resistor, a sixth capacitor, a seventh capacitor, an eighth capacitor, a ninth capacitor, a tenth capacitor, an eleventh capacitor, a base variable resistor, and a first operational amplifier; wherein, One end of the eighteenth resistor is connected to the positive preamplifier signal, and the other end of the eighteenth resistor is connected to one end of the nineteenth resistor, one end of the seventh capacitor, and the non-inverting input of the first operational amplifier; the other ends of the nineteenth resistor and the other end of the seventh capacitor are grounded. One end of the twentieth resistor is connected to the negative preamplifier signal and is connected to one end of the twentieth eleventh resistor and one end of the sixth capacitor, respectively. The other end of the twentieth resistor and the other end of the sixth capacitor are grounded. The other end of the twentieth resistor is connected to the inverting input terminal of the first operational amplifier, one end of the twentieth eleventh resistor, and one end of the eighth capacitor, respectively. The positive input terminal of the first operational amplifier is connected to the second operating voltage and is connected to one end of the ninth capacitor; the negative input terminal of the first operational amplifier is grounded and is connected to the other end of the ninth capacitor; the output terminal of the first operational amplifier is connected to the other end of the twenty-second resistor, the other end of the eighth capacitor, one end of the tenth capacitor, and one end of the twenty-third resistor, and is used to connect to the signal terminal of the signal comparison module. The other end of the 23rd resistor is connected to one end of the 24th resistor, one end of the 25th resistor, one end of the 26th resistor, and one end of the 11th capacitor, and is used to connect to the current control loop module; the other end of the 24th resistor is connected to the first fixed end of the base variable resistor, and the second fixed end of the base variable resistor, the movable end of the base variable resistor, the other end of the 10th capacitor, the other end of the 25th resistor, the other end of the 26th resistor, and the other end of the 11th capacitor are grounded.

9. The microsecond-level high-current laser driving circuit according to claim 3, characterized in that, The signal comparison unit includes: a first resistor, a second resistor, a third resistor, a fourth resistor, a fifth resistor, and a second operational amplifier; wherein, One end of the first resistor is connected to the pre-drive signal, and the other end of the first resistor is connected to one end of the third resistor and the inverting input terminal of the second operational amplifier, respectively. One end of the second resistor is connected to the first operating voltage, and the other end of the second resistor is connected to one end of the fourth resistor and the non-inverting input terminal of the second operational amplifier, respectively; the other ends of the third resistor and the other ends of the fourth resistor are grounded. The output of the second operational amplifier is connected to the first switching unit; One end of the fifth resistor is connected to the common terminal of the non-inverting input of the second operational amplifier and the fourth resistor, and the other end of the fifth resistor is connected to the output of the second operational amplifier.

10. A driver, characterized in that, Includes the microsecond-level high-current laser driving circuit and pump source circuit as described in any one of claims 1 to 9; wherein, The switch driving module of the microsecond-level high-current laser driving circuit is connected to the control terminal of the pump source circuit and is used to output the pump working signal or the pump turning off signal to the pump source circuit. The pump source circuit is used to collect and operate according to the pump working signal or the pump turning off signal, and output a current loop signal to the current control loop module.

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