Light-load high-reliability three-port active bridge energy co-transmission modulation method, device and system

Abstract

The application discloses a kind of light load high reliability three-port active bridge energy signal same transmission modulation method, device and system.For the problem that existing system loses soft switch excitation high-frequency common mode ringing under light load working condition, leading to serious degradation of physical channel, communication paralysis, the application proposes a kind of double-channel adaptive collaborative reconstruction strategy based on channel boundary evaluation.First, based on the critical current that maintains soft switch defines communication safety boundary;When output power is lower than the boundary, trigger collaborative reconstruction: frequency shift keying channel actively increases carrier frequency deviation and amplifies time domain decision margin window, and the adaptive dynamic integration threshold that is lifted in real time with load is introduced in differential phase shift keying channel to suppress noise floor deviation;In addition, the transient volt-second equalization mechanism of energy control layer eliminates frequency shift bias magnetism.The application breaks through the demodulation deadlock bottleneck under light load hard switch, guarantees the high reliable concurrent transmission of double-channel data under full working condition.

Description

Technical Field

[0001] This invention relates to the interdisciplinary field of power electronics and communication technology, and more specifically, to a lightweight, highly reliable three-port active bridge power signal modulation method, apparatus, and system. Background Technology

[0002] Three-port active-bridge (TAB) converters, with their advantages of electrical isolation, bidirectional power flow across multiple ports, and ease of soft switching, have been widely used in DC microgrids, integrated photovoltaic-storage systems, and energy routers. In these complex systems, not only is efficient power routing required between ports, but also a massive amount of status monitoring and scheduling command interaction. Traditional communication methods typically rely on additional independent communication cables or wireless communication modules. This not only increases the system's hardware size, wiring costs, and maintenance difficulty, but also highlights the vulnerability of external communication links in special operating scenarios such as deep-sea observation and aerospace, where high reliability, high power density, and stringent electromagnetic compatibility are paramount.

[0003] To address this, the technology of synchronous transmission of electrical energy and signals emerged. This technology reuses the existing physical hardware of the underlying power electronic converter, such as the power switching transistors and high-frequency transformers, and achieves concurrent transmission of electrical energy and information in the same physical medium by multiplexing high-frequency modulation signals in the power control commands.

[0004] However, existing TAB converter-based simultaneous signal transmission systems face two serious physical bottlenecks that severely restrict their industrial application when facing a wide range of load conditions:

[0005] First, there is the problem of severe degradation of the communication channel and even demodulation failure under light load or power drop conditions. In the actual operation of TAB converters, extremely light load is a very common condition. Under heavy load conditions, the converter can maintain a good ZVS state, and the physical channel is relatively clean; however, under light load conditions, due to the significant attenuation of the commutation current, the main circuit switching transistors lose the ZVS condition and enter a hard switching state. Hard switching instantaneously excites the parasitic parameters of the main circuit to generate severe high-frequency common-mode ringing, and superimposed with a slowed signal slew rate, resulting in severe distortion of the physical channel. Under this poor signal-to-noise ratio, the fixed frequency offset modulation and static demodulation decision threshold used by traditional simultaneous interpretation systems are difficult to adapt to. The receiver will generate a large amount of random time base jitter when extracting the zero crossing point, which will lead to large-scale demodulation deadlock and logic flip-flops, causing the communication system to be completely paralyzed under light load.

[0006] Second, there are issues with transient DC bias and power disturbance caused by high-frequency communication symbol transitions. In steady-state operation using conventional control strategies such as single-phase shift (SPS), the transformer winding voltage maintains symmetry between the positive and negative half-waves. However, during simultaneous communication and signal transmission, transient transitions in the communication carrier frequency directly disrupt the transient volt-second balance of the high-frequency transformer. Because traditional control loops lack transient compensation mechanisms for high-frequency symbol transitions, these transitions inevitably induce severe DC bias and low-frequency transient current surges at the physical level. This not only increases the transformer's core losses and the current stress on the switching transistors but may even trigger system overcurrent protection.

[0007] To solve the above problems, the conventional approach is often to add complex wave traps or high-frequency filter circuits to the hardware topology, but this fundamentally violates the original intention of the simultaneous transmission technology of "high power density and low hardware cost".

[0008] In view of this, how to completely solve the communication failure problem of TAB converter under light load and harsh operating conditions without increasing the size of any additional hardware, starting from the underlying control logic and modulation strategy, and at the same time eliminate the transient bias caused by frequency shift jump, so as to achieve lossless concurrent transmission of high-quality power and high-reliability data stream under all operating conditions, has become an urgent problem to be solved by those skilled in the art. Summary of the Invention

[0009] The purpose of this invention is to provide a light-load, high-reliability three-port active bridge converter with simultaneous communication modulation method, apparatus, and system, which solves the technical problems in the background art of demodulation paralysis caused by physical channel degradation of three-port active bridge converters under light-load conditions, and DC bias induced by communication carrier jump.

[0010] To achieve the above objectives, the technical solution of the present invention is as follows:

[0011] In a first aspect, the present invention provides a light-load, high-reliability three-port active bridge power-signal synchronous transmission modulation method. The method is applied to a three-port active bridge converter comprising three active full-bridge converters and a three-winding high-frequency transformer. During steady-state power transmission and synchronous transmission of electrical energy and signals via phase-shift control, the method includes the following steps: Obtain the real-time output power of the converter; Based on the critical conditions for soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, the physical channel security boundary is dynamically evaluated and the communication security critical threshold is determined. The real-time output power is compared with the critical threshold for communication security to divide the channel into a secure zone and a failure zone. When the real-time output power is within the channel safety zone, the frequency shift keying channel uses narrow frequency offset modulation, and the differential phase shift keying channel uses a fixed differential decision threshold for demodulation. When the real-time output power is in the channel failure region, the cooperative reconfiguration modulation mode is triggered: The frequency shift keying channel increases the carrier frequency offset and simultaneously widens the time-domain decision tolerance window at the receiver; The differential phase shift keying channel raises the integral decision threshold to an adaptive dynamic threshold in real time, and the adaptive dynamic threshold is negatively correlated with the real-time output power.

[0012] In some embodiments, the step of dynamically evaluating the physical channel security boundary and determining the communication security critical threshold based on the critical conditions of soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching includes: Extract the equivalent output capacitance and equivalent commutation inductance of the switching transistor, and calculate the critical draw-out current required to satisfy the zero-voltage turn-on of the switching transistor; Based on the voltage of each port, leakage inductance parameters, and the linear relationship between transient commutation current and output power in the small phase shift interval, the critical extraction current is substituted into the power calculation formula to solve for the critical power threshold for maintaining the soft switching operation of the load port. By combining the load-side filter capacitor, the initial amplitude of high-frequency common-mode ringing corresponding to light-load hard switching, and the system's maximum allowable time-domain decision tolerance, the theoretical limit power point at which irreversible communication demodulation failure occurs is solved. Then, by superimposing the preset engineering anti-interference power margin, the communication safety critical threshold in the hard-switching range below the soft-switching critical power is obtained.

[0013] In some embodiments, when a cooperative reconfiguration modulation mode is triggered, the receiver of the frequency shift keying channel extracts the time interval between the zero-crossing points of the received signal and widens the time-domain tolerance boundary used for state determination to shield the false zero-crossing edge introduced by high-frequency ringing.

[0014] In some embodiments, when the cooperative reconfiguration modulation mode is triggered, the differential phase shift keying channel extracts the time interval difference between adjacent carrier periods as a phase shift feature, and the adaptive dynamic threshold performs real-time dynamic compensation based on the difference between the current output power and the communication security critical threshold.

[0015] In some embodiments, the method further includes a frequency feedforward compensation step: extracting the current carrier frequency of the frequency shift keying channel, calculating the frequency feedforward coefficient and superimposing it onto the three-port phase shift control closed loop to compensate for power transmission fluctuations caused by carrier frequency changes.

[0016] In some embodiments, the method further includes: dynamically adjusting the phase shift control amount of the converter when a frequency shift keying jump occurs, so as to offset the volt-second product deviation caused by the frequency jump and suppress the DC bias of the high-frequency transformer.

[0017] In some embodiments, the dynamic adjustment of the phase shift control amount of the converter includes: Monitor the switching frequency jump triggered by the frequency shift keying communication symbol command. When the switching frequency changes from the original frequency to the target frequency by step, calculate the transient volt-second integral error of the transformer winding caused by the sudden change in the switching period at the beginning edge of the transient period of the frequency jump. Based on the transient volt-second integral error, combined with the original shift ratio before the jump, the target value of the steady-state shift ratio corresponding to constant power, the converted port DC voltage parameters, and the switching frequency jump ratio, the transient balance ratio corresponding to each port is calculated by the transient balance formula. By precisely injecting the transient balance ratio at the transition edge, the leakage inductance current satisfies the zero-mean constraint of the half-cycle volt-second integral at the transition moment, thus suppressing DC bias caused by frequency shift.

[0018] In some embodiments, the method further includes information scheduling based on data frame priority communication symbols, specifically including the following steps: Based on the smoothing and fault-tolerant characteristics of differential and polar integral operations on asymmetric noise floor in the differential phase shift keying channel, high-priority communication symbols of system faults and protection actions are mapped to the reconstructed differential phase shift keying channel for transmission. The low-priority communication symbols of routine status monitoring and background polling are mapped to the frequency shift keying channel in the large frequency offset mode for transmission; and the carrier period difference corresponding to the large frequency offset mode is set to meet the constraint condition to prevent the overlap of adjacent decision windows caused by time base jitter.

[0019] Secondly, the present invention provides a light-load, high-reliability three-port active bridge power-signal synchronous transmission modulation device. This device is applied to a three-port active bridge converter comprising three active full-bridge converters and a three-winding high-frequency transformer. During steady-state power transmission and synchronous transmission of electrical energy and signals via phase-shift control, the device includes: The boundary assessment module is used to obtain the real-time output power of the converter, dynamically assess the physical channel security boundary based on the critical conditions of soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, and determine the communication security critical threshold. The dual-channel collaborative reconfiguration module compares the real-time output power with the communication security critical threshold to divide the channel into a secure zone and a failed zone. When the real-time output power is in the secure zone, the frequency shift keying channel uses narrow frequency offset modulation, and the differential phase shift keying channel uses a fixed differential decision threshold for demodulation. When the real-time output power is in the failed zone, the collaborative reconfiguration modulation mode is triggered. The frequency shift keying channel increases the carrier frequency offset and simultaneously widens the time-domain decision tolerance window at the receiver; The differential phase shift keying channel raises the integral decision threshold to the adaptive dynamic threshold in real time, and the lower the output power, the higher the set value of the adaptive dynamic threshold.

[0020] Thirdly, the present invention provides a three-port active bridge signal-to-transmission converter system, the system comprising: Three-winding high-frequency transformer; Three active full-bridge circuits are connected to each winding of a three-winding high-frequency transformer, and each active full-bridge circuit consists of multiple switching transistors. The aforementioned lightweight, high-reliability three-port active bridge energy and signal synchronous transmission modulation device has its output terminal connected to the control terminal of the switching transistor, which is used to output a drive signal to control the switching transistor to turn on and off, thereby realizing the synchronous transmission of electrical energy and signals.

[0021] Beneficial effects of this invention: This invention employs a dual-channel adaptive collaborative reconfiguration based on channel boundary assessment. When the output power is below the communication security threshold, it actively increases the carrier frequency offset of the frequency shift keying channel and widens the time-domain decision tolerance window, while simultaneously raising the adaptive dynamic integration threshold of the differential phase shift keying channel. This mechanism can physically shield against false zero-crossing edges and asymmetric noise floor deviations introduced by high-frequency common-mode ringing. Without requiring additional high-frequency passive filtering hardware, it overcomes the demodulation deadlock bottleneck caused by the loss of soft switching in traditional simultaneous communication systems under light load conditions, achieving highly reliable concurrent data transmission across all operating conditions. Furthermore, this invention supplements the underlying control with a composite feedforward mechanism including steady-state Jacobian decoupling and transient volt-second balancing. For frequency jumps in frequency shift keying communication symbols, this mechanism forcibly resets the initial state of the leakage inductance current along the transient period, completely eliminating transient volt-second imbalance from the underlying layer. This not only significantly suppresses transient current overshoot and power fluctuations, but also perfectly avoids low-frequency DC bias, achieving deep decoupling and stable concurrency between electrical energy and signals. Attached Figure Description

[0022] To more clearly illustrate the technical solutions in the embodiments of the present invention or the prior art, the accompanying drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are merely some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without any creative effort.

[0023] Figure 1 This is a flowchart of a lightweight, high-reliability three-port active bridge signal modulation method according to an embodiment of the present invention.

[0024] Figure 2 This is a schematic diagram of the main circuit topology of the three-port active bridge (TAB) converter provided in an embodiment of the present invention;

[0025] Figure 3 This is an overall control block diagram of the multi-degree-of-freedom adaptive composite modulation system provided in the embodiments of the present invention;

[0026] Figure 4 This is a flowchart of the adaptive modulation and cooperative reconstruction control provided in the embodiments of the present invention;

[0027] Figure 5 This is a schematic diagram of the transient volt-second imbalance mechanism and transient feedforward compensation waveform under modulation step provided in the embodiments of the present invention;

[0028] Figure 6 This is a block diagram illustrating the principle of the hybrid time-domain demodulation architecture provided in this embodiment of the invention.

[0029] Figure 7 The above is an experimental waveform diagram of the system provided in this embodiment of the invention performing adaptive reconstruction of the frequency shift keying (FSK) channel under load drop conditions.

[0030] Figure 8 This is an experimental waveform diagram of the system provided in this embodiment of the invention performing adaptive reconstruction of differential phase shift keying channels under load drop conditions;

[0031] Figure 9 The experimental waveform diagram shows the system provided in this embodiment of the invention performing transient feedforward balancing to achieve power decoupling under sudden communication conditions.

[0032] Figure 10 The diagram shows the experimental waveforms of the system provided in this embodiment of the invention for real-time demodulation of dual-channel data streams under sudden communication conditions.

[0033] It should be noted that these accompanying drawings and textual descriptions are not intended to limit the scope of the invention in any way, but rather to illustrate the concept of the invention to those skilled in the art by referring to specific embodiments. Detailed Implementation

[0034] The technical solutions of the present invention will be clearly and completely described below with reference to the accompanying drawings in the embodiments of the present invention.

[0035] like Figure 1 As shown in the figure, an embodiment of the present invention illustrates a light-load, high-reliability three-port active bridge power-signal synchronous transmission modulation method. This method is applied to a three-port active bridge converter comprising three active full-bridge converters and a three-winding high-frequency transformer. During steady-state power transmission and synchronous transmission of electrical energy and signals through phase-shift control, the method includes the following steps:

[0036] Step S100: Obtain the real-time output power of the converter.

[0037] Specifically, the main output port of the converter is usually selected as the real-time output power. The sampling point is located after the DC bus capacitor and before the load at this port to avoid the impact of switching ripple on the sampling accuracy.

[0038] Step S200: Based on the criticality of soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, dynamically evaluate the physical channel security boundary and determine the communication security critical threshold.

[0039] In this embodiment of the application, step S200 includes the following steps:

[0040] Step S210: Extract the equivalent output capacitance and equivalent commutation inductance of the switching transistor, and calculate the critical draw-out current required to satisfy the zero-voltage turn-on of the switching transistor.

[0041] Specifically, extract the equivalent output capacitance of the switching transistor. With equivalent commutation inductance ,use Calculate the critical draw current required to achieve zero-voltage turn-on, where It is the minimum critical drawdown current required for the load port switch to achieve zero-voltage turn-on, and it is the core current threshold for determining whether soft switching can be achieved. This is the converted DC voltage at the port.

[0042] Step S220: Based on the voltage and leakage inductance parameters of each port, and considering the approximate linear relationship between the transient commutation current and the total output power in the small phase shift interval, substitute the critical extraction current into the formula. Calculate the critical power threshold corresponding to maintaining soft switching at the load port, where This is the DC voltage at the port.

[0043] When the real-time output power is lower than the critical power threshold At that time, the converter enters the hard-switching range and triggers high-frequency common-mode ringing interference at the moment of commutation.

[0044] Step S230: Combining the load-side filter capacitor, the initial amplitude of high-frequency common-mode ringing corresponding to light-load hard switching, and the system's maximum allowable time-domain decision tolerance, the theoretical limit power point at which irreversible communication demodulation failure occurs is solved by inverse solution, and the preset engineering anti-interference power margin is superimposed to obtain the communication safety critical threshold in the hard switching range below the soft switching critical power.

[0045] Specifically, to address the physical channel degradation phenomenon within the hard-switching interval, the load-side filter capacitor is obtained. Initial amplitude of high-frequency common-mode ringing under light-load hard switching Combined with the maximum time-domain decision tolerance allowed by the system The jitter of the communication signal at the zero-crossing point caused by high-frequency ringing. ,make The theoretical limiting power point at which the conventional signal experiences irreversible demodulation failure is determined by inverse solving. On this basis, an engineering disturbance rejection power margin is added. Finally, the critical threshold for communication security was determined. ,Right now .

[0046] Step S300: Compare the real-time output power with the communication security critical threshold to divide the channel security zone and the channel failure zone.

[0047] Furthermore, when the real-time output power ≥ Communication security critical threshold When the channel is deemed safe, the real-time output power is determined to be within the safe zone. <Communication security critical threshold> When this occurs, it is determined to be a channel failure zone.

[0048] Step S400: When the real-time output power is within the channel safety zone, the frequency shift keying channel uses narrow frequency offset modulation, and the differential phase shift keying channel uses a fixed differential decision threshold for demodulation.

[0049] Step S500: When the real-time output power is in the channel failure region, trigger the cooperative reconstruction modulation mode:

[0050] The frequency shift keying channel increases the carrier frequency offset and simultaneously widens the time-domain decision tolerance window at the receiver; the differential phase shift keying channel raises the integration decision threshold to the adaptive dynamic threshold in real time, and the adaptive dynamic threshold is negatively correlated with the real-time output power.

[0051] The adaptive dynamic threshold and real-time output power are negatively correlated, expressed as: Output Power The smaller the value, the more adaptive the dynamic threshold. The higher the setting value, the better.

[0052] This invention raises the integral decision threshold to an adaptive dynamic threshold in real time through a differential phase shift keying channel. and output power The smaller, The higher the setting value, the better to mitigate logic flip-flops caused by the accumulation of asymmetric background noise.

[0053] Furthermore, when the cooperative reconstruction modulation mode is triggered, the receiver of the frequency shift keying channel extracts the time interval between the zero-crossing points of the received signal. Widen the temporal tolerance boundary used for state decision This is to shield against false zero-crossing edges introduced by high-frequency ringing.

[0054] Furthermore, when the cooperative reconstruction modulation mode is triggered, the differential phase shift keying channel extracts the time interval difference between adjacent carrier periods as a phase shift feature, and adaptively sets the dynamic threshold. Based on the current output power and the critical threshold for communication security The difference is dynamically compensated in real time.

[0055] When the controller determines that the system has entered the channel failure zone, it will automatically start the dual-channel collaborative reconfiguration program.

[0056] Specifically, for the Frequency Shift Keying (FSK) channel, the controller actively increases the frequency offset between different logic frequencies at the transmitter. At the receiver, the controller synchronously executes tolerance amplification logic to widen the time-domain tolerance boundary used for state decision. This amplification of the time-domain physical characteristic difference effectively shields the false zero-crossing signal generated by high-frequency ringing at the carrier edge, ensuring demodulation lock-in under poor signal-to-noise ratio conditions. Meanwhile, for the Differential Phase Shift Keying (DPSK) channel, the controller introduces an adaptive dynamic threshold. The threshold rises in real time as the load current decreases to effectively accommodate the accumulated deviation caused by asymmetric noise within the integration window and to smooth out random flips in the demodulation logic.

[0057] In an optional embodiment, the method further includes step S600: when a frequency shift keying symbol jumps, dynamically adjust the phase shift control amount of the converter to offset the volt-second product deviation caused by the frequency jump and suppress the DC bias of the high-frequency transformer.

[0058] In this embodiment of the application, dynamically adjusting the phase shift control amount of the converter includes:

[0059] Step S610: Monitor the frequency transitions generated by the frequency shift keying communication symbol communication command. When the switching frequency changes from the original frequency... Step to target frequency At the beginning edge of the transient period of frequency jump, calculate the transient volt-second integral error of the transformer winding caused by the sudden change in the switching period.

[0060] Step S620: Based on the transient volt-second integral error, combined with the original shift ratio before the jump, the target value of the steady-state shift ratio corresponding to constant power, the converted port DC voltage parameters, and the switching frequency jump ratio, the transient balance ratio corresponding to each port is calculated using the transient balance formula.

[0061] Furthermore, based on the transient volt-second integral error, the transient balance ratio for port j is calculated using the transient balance formula. The specific calculation formula is as follows:

[0062]

[0063] In the formula, Compared to the original shift before the frequency jump, To ensure that the steady-state shift ratio remains constant before and after the jump, and These are the converted source port and load port DC voltages, respectively; and the transient balance ratio is... The impulse function is superimposed on the steady-state shift ratio, and the shift ratio is adapted to the operating condition. Reset the initial value of the leakage inductance current of the high-frequency transformer, where For steady-state Jacobian decoupling feedforward compensation, This refers to the discrete moment of the jump in the composite modulation communication command. This represents the discrete control time sequence number. It is a discrete unit impulse function.

[0064] Step S630: By precisely injecting the transient balancing ratio at the transition edge. This ensures that the leakage inductance current satisfies the zero-mean constraint of the half-cycle volt-second integral at the transition moment, thus suppressing DC bias caused by frequency shift.

[0065] In another optional embodiment, the method further includes step S700: information scheduling based on data frame priority communication symbols.

[0066] In this embodiment of the application, information scheduling based on data frame priority specifically includes the following steps:

[0067] Step S710: Based on the smoothing and fault-tolerant characteristics of differential and polar integral operations on asymmetric noise floor in the differential phase shift keying channel, high-priority communication symbols of system faults and protection actions are mapped to the reconstructed differential phase shift keying channel for transmission.

[0068] Step S720: Map the low-priority communication symbols of regular status monitoring and background polling to the frequency shift keying channel in the large frequency offset mode for transmission; and set the carrier period difference corresponding to the large frequency offset mode to meet the constraint conditions to prevent the overlap of adjacent decision windows caused by time base jitter.

[0069] Specifically, low-priority communication symbols for routine status monitoring and background polling are mapped to the frequency shift keying channel in large frequency offset mode for transmission; wherein, the carrier period difference corresponding to the large frequency offset mode is set to meet the constraint conditions. To prevent time base jitter from causing adjacent decision windows to overlap, in the formula and These are the carrier periods corresponding to large frequency offsets. This represents the maximum time base jitter.

[0070] The following is an embodiment of a lightweight, high-reliability three-port active bridge simultaneous signaling modulation device according to the present invention, which can be used to execute an embodiment of a lightweight, high-reliability three-port active bridge simultaneous signaling modulation method according to the present invention. For details not disclosed in the embodiment of the lightweight, high-reliability three-port active bridge simultaneous signaling modulation device according to the present invention, please refer to the embodiment of the lightweight, high-reliability three-port active bridge simultaneous signaling modulation method according to the present invention.

[0071] In one embodiment, a light-load, high-reliability three-port active bridge power-signal synchronous transmission modulation device is provided. This device is applied to a three-port active bridge converter comprising three active full-bridge converters and a three-winding high-frequency transformer. During steady-state power transmission and synchronous transmission of electrical energy and signals via phase-shift control, the device includes:

[0072] The boundary assessment module is used to obtain the real-time output power of the converter, dynamically assess the physical channel security boundary based on the critical conditions of soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, and determine the communication security critical threshold.

[0073] The dual-channel collaborative reconfiguration module compares the real-time output power with the communication security critical threshold to divide the channel into a secure zone and a failed zone. When the real-time output power is in the secure zone, the frequency shift keying channel uses narrow frequency offset modulation, and the differential phase shift keying channel uses a fixed differential decision threshold for demodulation. When the real-time output power is in the failed zone, the collaborative reconfiguration modulation mode is triggered.

[0074] The frequency shift keying channel increases the carrier frequency offset and simultaneously widens the time-domain decision tolerance window at the receiver;

[0075] The differential phase shift keying channel raises the integral decision threshold to the adaptive dynamic threshold in real time, and the lower the output power, the higher the set value of the adaptive dynamic threshold.

[0076] In an optional embodiment, the boundary assessment module is further configured to:

[0077] Extract the equivalent output capacitance and dead time of the switching transistor, and calculate the critical draw current required to satisfy zero-voltage turn-on.

[0078] Based on the voltage and leakage inductance parameters of each port, the critical extraction current is substituted into the power transfer equation, and the corresponding critical power threshold is solved in reverse.

[0079] By combining the critical power threshold with the failure power tolerance corresponding to the time base jitter caused by high-frequency common-mode ringing, the critical threshold for communication security is determined.

[0080] Furthermore, when the dual-channel collaborative reconstruction module triggers the collaborative reconstruction modulation mode, it is also used to control the time interval for the receiver of the frequency shift keying channel to extract the zero-crossing point of the received signal, and to widen the time-domain tolerance boundary used for state decision, so as to shield the false zero-crossing edge introduced by high-frequency ringing.

[0081] Furthermore, when the dual-channel collaborative reconstruction module triggers the collaborative reconstruction modulation mode, it is also used to control the differential phase shift keying channel to extract the time interval difference between adjacent carrier periods as a phase shift feature, and the adaptive dynamic threshold is used to perform real-time linear compensation based on the difference between the current output power and the communication security critical threshold.

[0082] In an optional embodiment, the device further includes a frequency feedforward compensation module for extracting the current carrier frequency of the frequency shift keying channel, calculating the frequency feedforward coefficient, and superimposing it onto the three-port phase shift control closed loop to compensate for power transmission fluctuations caused by carrier frequency changes.

[0083] In an optional embodiment, the device further includes a transient volt-second balancing module, which dynamically adjusts the phase shift control amount of the converter when a frequency shift keying symbol jumps, so as to offset the volt-second product deviation caused by the frequency jump and suppress the DC bias of the high-frequency transformer.

[0084] Furthermore, the transient volt-second balance module is also used for:

[0085] Monitor the frequency jumps generated by communication symbols, and calculate the duty cycle error caused by the frequency shift during the transient period of the frequency jump;

[0086] The transient balance ratio is determined based on the duty cycle error, and the transient balance ratio is superimposed on the steady-state shift ratio to reset the initial value of the leakage inductance current of the high-frequency transformer.

[0087] This ensures that the leakage inductance current satisfies the zero-mean constraint of the half-cycle volt-second integral at the transition moment, thus suppressing DC bias caused by frequency shift.

[0088] In an optional embodiment, the device further includes an information scheduling module, which maps high-priority commands such as system faults and protection actions to the reconstructed differential phase shift keying channel for transmission, and maps low-priority commands such as routine monitoring and background polling to the frequency shift keying channel for transmission.

[0089] In one embodiment, a three-port active bridge signal transceiver system is provided, the system comprising:

[0090] Three-winding high-frequency transformer;

[0091] Three active full-bridge circuits are connected to each winding of a three-winding high-frequency transformer, and each active full-bridge circuit consists of multiple switching transistors.

[0092] A lightweight, high-reliability three-port active bridge energy and signal synchronous transmission modulation device has its output terminal connected to the control terminal of a switching transistor. It is used to output a drive signal to control the switching transistor to turn on and off, thereby realizing the synchronous transmission of electrical energy and signals.

[0093] It should be noted that the description of the light-load, high-reliability three-port active bridge signaling modulation device is the same as described in the above embodiment, and will not be repeated here.

[0094] Furthermore, the system also includes a hardware execution platform, which includes a digital signal processor, a high-frequency transformer drive unit connected to the digital signal processor, and an analog front-end circuit for receiving and conditioning the simultaneous transmission signal. The analog front-end circuit includes an active filter unit and a high-speed comparator unit connected in series, which are used to convert the high-frequency coupled signal into a square wave and input it to the digital acquisition unit of the digital signal processor for time-domain feature extraction.

[0095] The three-port active bridge (TAB) converter in this embodiment enables simultaneous signal transmission and communication. Its physical hardware foundation is as follows: Figure 2 As shown. The core of the system consists of three active full-bridge circuits magnetically coupled through three-winding high-frequency transformers. Each bridge arm is composed of power electronic switching transistors with controlled characteristics. Port 1: A DC voltage source is provided on the DC side. With DC support capacitor Parallel connection, port input current is ; by switching transistor This forms the first group of single-phase active full-bridge circuits, with the upper and lower midpoints of the bridge arms being A and B, respectively. The output bridge arm AC voltage is... ; Equivalent leakage inductance in series at the output end of the bridge arm Then, the first primary winding of the three-winding high-frequency transformer is connected, and the winding-side current is... Port 2: DC voltage source is installed on the DC side. With DC support capacitor Parallel connection, port input current is ; by switching transistor This forms the second single-phase active full-bridge circuit, with the upper and lower midpoints of the bridge arms being C and D, respectively, and the output bridge arm AC voltage. ; Equivalent leakage inductance in series at the output end of the bridge arm Then, it is connected to the second primary winding of the three-winding high-frequency transformer, and the winding-side current is... Port 3: Equivalent leakage inductance of the secondary winding in series with a three-winding high-frequency transformer. The winding side current is ; by switching transistor This forms the third group of single-phase active full-bridge circuits, with the upper and lower midpoints of the bridge arms being E and F, respectively, and the AC voltage of the bridge arms being... A load-side filter capacitor is connected in parallel at the DC output terminal of the full-bridge bridge. The subsequent stage is connected to a load, and the port output current is... The core of the system consists of three active full-bridge circuits magnetically coupled through three-winding high-frequency transformers. Each bridge arm is composed of power electronic switches with controllable characteristics. The system's intelligent logic operates in a connected controller, which not only achieves closed-loop power control by sampling the DC voltage and output current of each port, but also achieves coordinated modulation through its integrated energy control layer and information demodulation layer.

[0096] See Figure 3 The diagram illustrates the closed-loop control block diagram of a multi-degree-of-freedom adaptive composite modulation system. The adaptive frequency offset switching unit outputs the communication safety critical threshold to the adaptive frequency offset switching in this diagram. The dual-channel collaborative reconfiguration module outputs channel partition control commands to the FSK mapping and receiver demodulation unit, together forming a complete closed-loop control system. The energy control layer is based on a single-phase-shift (SPS) modulation mechanism, using a steady-state Jacobian decoupling matrix to convert the phase shift between each port into independent power control variables. The information layer is responsible for embedding and extracting communication symbols from these high-frequency drive signals. The specific working principle is as follows: The system simultaneously receives the FSK communication data to be transmitted. Data communication with DPSK and voltage sampling values ​​at each port of the converter. Current sampling value and port reference value , The frequency offset control command output by the adaptive frequency offset switching of the input operating condition and the FSK communication data to be transmitted are... This maps binary communication data to two different carrier frequencies. The channel security zone corresponds to the first frequency offset. (carrier frequency) The channel failure region corresponds to the second frequency offset. (carrier frequency) ),and Output carrier frequency Simultaneously, the signal is sent in three channels to the frequency feedforward, transient volt-second balance feedforward, and multi-degree-of-freedom PWM generator. The input FSK is mapped to the output carrier frequency. According to the formula Calculate the frequency feedforward coefficients (where (This is the system reference switching frequency), and this coefficient is superimposed on the three-port phase-shift control closed loop to compensate for power transmission fluctuations caused by carrier frequency changes, ensuring power balance and output voltage stability at each port of the three-port active bridge. The voltage reference value is then... With sampling voltage The difference, current reference value With sampling current The difference is fed into the regulator to obtain two initial control quantities. After power decoupling processing, combined with the frequency feedforward compensation, the final steady-state shift ratio is obtained as the reference. The decoupled control quantity is multiplied by the frequency-dependent gain unit. Feedforward compensation is performed to obtain a steady-state shift ratio reference. The carrier frequency of the FSK mapping output is monitored in real time. At the transition edge of the frequency jump, at the start edge of the transient period of the frequency jump, calculate the duty cycle error caused by the frequency shift; determine the transient balance ratio of the two paths based on the duty cycle error. and These correspond to the phase shift compensation amounts at the respective ports. The transient balance ratio... The final shift ratio is obtained by superimposing the shift ratios to the steady-state shift ratios. Transient balancing ratio The final shift ratio is obtained by superimposing the shift ratios to the steady-state shift ratios. The initial value of the leakage inductance current of the high-frequency transformer is reset so that the leakage inductance current satisfies the zero-mean constraint of the half-cycle volt-second integral at the transition moment, eliminating the DC bias magnetization caused by frequency shift. The communication phase reference is input to the DPSK phase modulation branch output. Final move compared and Generates six independent PWM drive signals The switching transistors of the upper and lower arms of the three active full-bridge circuits are controlled to turn on and off, and the electrical energy and communication signals are synchronously coupled to the three-winding high-frequency transformer to achieve synchronous transmission of electrical energy and signals.

[0097] Figure 4 The flowchart of the dual-channel adaptive collaborative reconfiguration algorithm of the light-load, high-reliability three-port active bridge power-information co-modulation method described in this invention illustrates the core decision-making logic and execution flow of the operating condition adaptive modulation. The specific working principle is as follows: The system first acquires the converter's operating parameters in real time, including the real-time output power. , port 3 voltage and the steady-state shift between ports compared to , Then assess the communication security tolerance boundaries and determine the real-time output power. Is it greater than or equal to the communication security critical threshold? If the determination result is yes, the system enters the channel security zone and operates in mode 1, transparent modulation distribution: the physical layer maintains the original modulation parameters and keeps the FSK channel frequency offset at the minimum frequency offset. The information layer adopts a conventional data allocation strategy, and conventional monitoring and control data can be transmitted concurrently through FSK or DPSK dual channels. If the judgment result is negative, the system enters the conventional failure zone, and the operating mode 2, collaborative reconstruction modulation, is activated: the physical layer performs noise-resistant adaptive adjustment, increasing the frequency offset of the FSK channel to the maximum frequency offset. The information layer maintains dual-channel concurrency and performs priority scheduling, mapping high-priority commands such as system faults and protection actions to the more interference-resistant DPSK channel for transmission, and mapping low-priority commands such as routine monitoring and background polling to the high-frequency-offset FSK channel for transmission. Finally, the modulation parameters of the two modes are adaptively combined into a composite signal to generate the final switching transistor drive signal sequence, achieving coordinated optimization of power transmission efficiency and communication reliability under all operating conditions. While handling information layer reconstruction, in order to eliminate the transient impact of communication frequency jumps on power transmission quality, the energy control layer simultaneously initiates a transient volt-second balancing mechanism.

[0098] like Figure 5 As shown, when the FSK symbol switches carrier frequencies, the original periodic balance of the transformer is instantly disrupted, easily inducing magnetization. At this time, the controller injects a compensation ratio within the transient period after the transition edge triggering. This compensation ratio is used to finely adjust the duty cycle of the drive pulse, forcibly reset the initial state of the transient magnetic flux of the transformer winding, so that it meets the zero mean constraint of the half-cycle volt-second integral, thereby ensuring the stability of the main circuit current and power transmission while performing high-frequency communication symbol switching, and realizing true signal-energy decoupling.

[0099] The final hardware extraction process of the data is as follows Figure 6 The hybrid time-domain demodulation architecture shown is supported. The signal conditioning circuit extracts the analog signal containing information from the transformer port, filters out power components and noise glitches through an active filter, and then converts it into a square wave pulse sequence that the controller can recognize through a high-speed comparator circuit. The controller uses the aforementioned adaptive decision mechanism to complete data extraction. The specific working principle is as follows: The system extracts the load voltage signal containing communication information from the converter load branch. As input, the first input is a passband range of... A bandpass filter (BPF) is used to filter out the DC power component and switching harmonic noise, extracting an analog AC voltage signal containing only the communication frequency component. This analog signal is then input to a hysteresis comparator and converted into a standard digital square wave signal. This effectively suppresses false triggering caused by signal amplitude fluctuations; then, the digital square wave signal is sent to a digital anti-jitter filter for noise reduction, filtering out narrow pulse spikes introduced by high-frequency ringing; finally, the carrier period measurement value is obtained by capturing and timing the time interval between adjacent edges of the square wave. ; Periodic measurement value Simultaneously, the signals are fed into the FSK window decision unit and the DPSK differential decision unit for dual-channel demodulation: in the FSK demodulation branch, Respectively with the carrier frequency of the safe zone Corresponding nominal period The nominal period corresponding to the carrier frequency f2 in the failure zone Compare, when satisfied The decision outputs binary data 0 when the condition is met. The decision outputs binary data 1, where For adaptively adjustable time-domain decision tolerance; in the DPSK demodulation branch, the current period measurement value is... With scriptures The measurement value of the previous cycle obtained by the delay unit The difference is obtained by subtracting the periodic difference. When satisfied The decision is to invert the phase and output binary data 1 when the condition is met. The timing decision is to continuously output binary data 0, where This is a differential decision threshold that can be adaptively raised according to the output power. This demodulation scheme adopts a pure time-domain zero-crossing detection architecture, which does not require complex frequency domain transformation, has low computational load, high real-time performance, can be directly implemented on a general digital signal processor, and the decision parameters can be adaptively adjusted in coordination with the transmitting side, perfectly adapting to the communication needs under all working conditions.

[0100] The technical effects of the embodiments of the present invention are as follows: Figures 7 to 10 The experimental waveforms were verified: see Figure 7 As shown, this illustrates the converter's output power from... Towards extremely light load The FSK demodulated waveform under dynamic power step conditions. Before the power step, the system operates in normal frequency offset mode. At the instant the step occurs, the output current... Rapid drop, hard switching induces load voltage ripple after filtering The surge generates high-frequency ringing and breaks through the conventional decision threshold. At this point, the system automatically switches to a large-frequency offset cooperative windowing mode to reshape the square wave signal. Corresponding judgment tolerance Dynamic widening prevents decision window overlap caused by time base jitter, thus improving the FSK receive demodulation sequence. No errors occurred throughout the transient and light load processes.

[0101] See Figure 8 The image shows the DPSK demodulation waveform under the same power step condition. After the load suddenly drops to 20W, the asymmetric noise floor spikes. The system uses a dynamic integration threshold mechanism to adjust the differential decision threshold. Dynamically and adaptively adjusting the output power based on variations avoids the time base jitter interference region, thus improving the DPSK receiver demodulation sequence. It can accurately identify phase inversion and phase continuity states, and achieve reliable demodulation under light load.

[0102] See Figure 9 As shown, the transient volt-second balancing feedforward mechanism is demonstrated in the FSK transmitted symbol sequence. The control effect at the frequency transition moment. By injecting a transient balancing ratio at the frequency transition edge, the current on one side of the transformer is controlled. During abrupt changes in the switching cycle, the signal rapidly converges to a new steady state. Within the volt-second forced balancing region, there is no significant large-scale transient current drift, resulting in a smooth transition of the output voltage ripple. This eliminates power disturbances and magnetization caused by frequency shift, and improves the FSK receiver demodulation sequence. Maintain high fidelity.

[0103] See Figure 10 As shown, this further confirms the system's ability to transmit symbol sequences in DPSK. Under sudden communication conditions, due to the introduction of corresponding transient bias suppression in the phase misalignment disturbance region, the transformer current... Maintaining symmetrical fluctuations, the output voltage ripple was not distorted, and the system achieved real-time accurate concurrent demodulation of dual-channel data streams.

[0104] The above description is merely a preferred embodiment of the present invention and is not intended to limit the present invention in any way. Although the present invention has been disclosed above with reference to preferred embodiments, it is not intended to limit the present invention. Any person skilled in the art can make some modifications or alterations to the above-described technical content to create equivalent embodiments without departing from the scope of the present invention. Any simple modifications, equivalent changes, and alterations made to the above embodiments based on the technical essence of the invention without departing from the scope of the present invention shall still fall within the scope of the present invention.

Claims

1. A lightweight, high-reliability three-port active bridge signal modulation method, characterized in that: The method is applied to a three-port active bridge converter containing three active full-bridge converters and a three-winding high-frequency transformer. During steady-state power transfer and synchronous transmission of electrical energy and signals via phase-shift control, the method includes the following steps: Obtain the real-time output power of the converter; Based on the critical conditions for soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, the physical channel security boundary is dynamically evaluated and the communication security critical threshold is determined. The real-time output power is compared with the critical threshold for communication security to divide the channel into a secure zone and a failure zone. When the real-time output power is in the channel safe zone, the frequency shift keying channel uses narrow frequency offset modulation, and the differential phase shift keying channel uses a fixed differential decision threshold for demodulation. When the real-time output power is in the channel failure region, the cooperative reconfiguration modulation mode is triggered: The frequency shift keying channel increases the carrier frequency offset and simultaneously widens the time-domain decision tolerance window at the receiver; The differential phase shift keying channel raises the integral decision threshold to an adaptive dynamic threshold in real time, and the adaptive dynamic threshold is negatively correlated with the real-time output power.

2. The lightweight, high-reliability three-port active bridge signaling modulation method according to claim 1, characterized in that: The method dynamically evaluates the physical channel security boundary based on the critical conditions of soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, and determines the communication security critical threshold, including: Extract the equivalent output capacitance and equivalent commutation inductance of the switching transistor, and calculate the critical draw-out current required to satisfy the zero-voltage turn-on of the switching transistor; Based on the voltage of each port, leakage inductance parameters, and the linear relationship between transient commutation current and output power in the small phase shift interval, the critical extraction current is substituted into the power calculation formula to solve for the critical power threshold for maintaining the soft switching operation of the load port. By combining the load-side filter capacitor, the initial amplitude of high-frequency common-mode ringing corresponding to light-load hard switching, and the system's maximum allowable time-domain decision tolerance, the theoretical limit power point at which irreversible communication demodulation failure occurs is solved. Then, by superimposing the preset engineering anti-interference power margin, the communication safety critical threshold in the hard-switching range below the soft-switching critical power is obtained.

3. The lightweight, high-reliability three-port active bridge signaling modulation method according to claim 1, characterized in that: When the cooperative reconstruction modulation mode is triggered, the receiver of the frequency shift keying channel extracts the time interval of the zero-crossing point of the received signal and widens the time-domain tolerance boundary used for state decision to shield the false zero-crossing edge introduced by high-frequency ringing.

4. The lightweight, high-reliability three-port active bridge modulation method according to claim 1, characterized in that: When the cooperative reconfiguration modulation mode is triggered, the differential phase shift keying channel extracts the time interval difference between adjacent carrier periods as a phase shift feature, and the adaptive dynamic threshold performs real-time dynamic compensation based on the difference between the current output power and the communication security critical threshold.

5. The lightweight, high-reliability three-port active bridge signaling modulation method according to claim 1, characterized in that: The method further includes a frequency feedforward compensation step: extracting the current carrier frequency of the frequency shift keying channel, calculating the frequency feedforward coefficient, and superimposing it onto the three-port phase shift control closed loop to compensate for power transmission fluctuations caused by carrier frequency changes.

6. The lightweight, high-reliability three-port active bridge modulation method according to claim 1, characterized in that: The method further includes: dynamically adjusting the phase shift control quantity of the converter when a frequency shift keying jump occurs, so as to offset the volt-second product deviation caused by the frequency jump and suppress the DC bias of the high-frequency transformer.

7. The lightweight, high-reliability three-port active bridge modulation method according to claim 6, characterized in that: The phase shift control quantity of the dynamically adjusted converter includes: Monitor the switching frequency jump triggered by the frequency shift keying communication symbol command. When the switching frequency changes from the original frequency to the target frequency by step, calculate the transient volt-second integral error of the transformer winding caused by the sudden change in the switching period at the beginning edge of the transient period of the frequency jump. Based on the transient volt-second integral error, combined with the original shift ratio before the jump, the target value of the steady-state shift ratio corresponding to constant power, the converted port DC voltage parameters, and the switching frequency jump ratio, the transient balance ratio corresponding to each port is calculated by the transient balance formula. By precisely injecting the transient balance ratio at the transition edge, the leakage inductance current satisfies the zero-mean constraint of the half-cycle volt-second integral at the transition moment, thus suppressing DC bias caused by frequency shift.

8. The lightweight, high-reliability three-port active bridge modulation method according to claim 6, characterized in that: The method also includes information scheduling based on data frame priority communication symbols, specifically including the following steps: Based on the smoothing and fault-tolerant characteristics of differential and polar integral operations on asymmetric noise floor in the differential phase shift keying channel, high-priority communication symbols of system faults and protection actions are mapped to the reconstructed differential phase shift keying channel for transmission. The low-priority communication symbols of routine status monitoring and background polling are mapped to the frequency shift keying channel in the large frequency offset mode for transmission; and the carrier period difference corresponding to the large frequency offset mode is set to meet the constraint condition to prevent the overlap of adjacent decision windows caused by time base jitter.

9. A lightweight, high-reliability three-port active bridge signal transduction modulation device, characterized in that: The device is applied to a three-port active bridge converter comprising three active full-bridge converters and a three-winding high-frequency transformer. During steady-state power transmission and synchronous transmission of electrical energy and signals via phase-shift control, the device includes: The boundary assessment module is used to obtain the real-time output power of the converter, dynamically assess the physical channel security boundary based on the critical conditions of soft switching of the switching transistor and the time base jitter caused by high-frequency common-mode ringing under light load hard switching, and determine the communication security critical threshold. The dual-channel collaborative reconfiguration module compares the real-time output power with the communication security critical threshold to divide the channel into a secure zone and a failed zone. When the real-time output power is in the secure zone, the frequency shift keying channel uses narrow frequency offset modulation, and the differential phase shift keying channel uses a fixed differential decision threshold for demodulation. When the real-time output power is in the failed zone, the collaborative reconfiguration modulation mode is triggered. The frequency shift keying channel increases the carrier frequency offset and simultaneously widens the time-domain decision tolerance window at the receiver; The differential phase shift keying channel raises the integral decision threshold to the adaptive dynamic threshold in real time, and the lower the output power, the higher the set value of the adaptive dynamic threshold.

10. A three-port active bridge signal transceiver system, characterized in that, The system includes: Three-winding high-frequency transformer; Three active full-bridge circuits are connected to each winding of a three-winding high-frequency transformer, and each active full-bridge circuit consists of multiple switching transistors. The lightweight, high-reliability three-port active bridge energy and signal synchronous transmission modulation device according to claim 9 has its output terminal connected to the control terminal of the switching transistor, used to output a drive signal to control the switching transistor to turn on and off, thereby realizing the synchronous transmission of electrical energy and signal.

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