Gain control method, electronic device, storage medium, and program product

Abstract

The application provides a gain control method, an electronic device, a storage medium and a program product, and relates to the technical field of communication. The method simultaneously obtains received signal strength indicators and aligns them to a unified reference system after a plurality of observation nodes, namely, an analog front end, an analog-to-digital converter output end and a baseband filter, thereby effectively solving the problems of incomplete single-point detection information and the inability to directly compare multi-domain powers in the prior art, and achieving comprehensive perception of in-band signals, out-of-band interference and thermal noise. On this basis, the theoretical gain adjustment amount is determined according to the signal strength of the aligned analog-to-digital converter output end, and the distribution of analog gain and digital gain is jointly decided in combination with multi-domain information, thereby providing a strong basis for gain distribution decision and improving the reliability of gain distribution.

Description

Technical Field

[0001] This application relates to the field of communication technology, and more specifically, to a gain control method, electronic device, storage medium, and program product. Background Technology

[0002] In fourth-generation (4G) and fifth-generation (5G) cellular communication systems, terminal receivers need to operate normally in extremely complex electromagnetic environments. Communication standards such as LTE (Long Term Evolution), NB-IoT (Narrow Band Internet of Things), and NR (New Radio) present terminal devices in various scenarios, including urban canyons, deep indoor spaces, and high-speed movement, resulting in a wide dynamic range of received signal power due to drastic changes in the propagation environment. Specifically, path loss and shadowing fading cause power fluctuations exceeding 100dB as the signal propagation distance changes; multipath effects lead to frequency-selective fading when the signal reaches the receiver via different paths; adjacent-channel communication systems or out-of-band blocking signals may fall into the receiving frequency band or adjacent channels, causing strong interference; and the base station's dynamic adjustment of transmit power based on channel conditions further exacerbates the uncertainty of the received signal. To cope with this dynamic range and ensure that the effective signal power received by the baseband processing unit remains at an appropriate level, terminal receivers typically need to be configured with an Automatic Gain Control (AGC) mechanism.

[0003] In existing terminal AGC implementations, a feedback control architecture based on Received Signal Strength Indicator (RSSI) is commonly used. Most existing solutions only detect the RSSI of a single observation node, which only provides local power information at that single node. Since the signal composition differs at each node in the receiving link, single-point detection cannot fully reflect the complete spectral characteristics of the received signal, resulting in insufficient basis for gain control decisions. Summary of the Invention

[0004] The purpose of this application is to provide a gain control method, electronic device, storage medium, and program product to improve the problem that single-point RSSI detection in the prior art cannot fully reflect the complete spectral characteristics of the received signal, resulting in insufficient decision-making basis for gain control.

[0005] In a first aspect, embodiments of this application provide a gain control method applied to a terminal, the method comprising: The received signal strength indications of multiple different observation nodes in the receiver are obtained, where the observation nodes are located after the analog front end, the analog-to-digital converter output, and the baseband filter, respectively. Based on the link gain corresponding to each observation node, the received signal strength indication is aligned to a unified reference frame; Based on the received signal strength indication at the output of the aligned analog-to-digital converter, determine the theoretical gain adjustment amount that the receiver needs to achieve; Based on the received signal strength indications after alignment and the theoretical gain adjustment, determine the analog gain and digital gain to be configured; The analog gain and the digital gain are respectively configured to the corresponding devices so that gain control can be performed using the analog gain and the digital gain in the next gain control cycle.

[0006] In the above implementation process, by simultaneously acquiring the received signal strength indication at multiple observation nodes, namely the analog front-end, the analog-to-digital converter output, and the baseband filter, and aligning it to a unified reference frame, the problems of incomplete single-point detection information and the inability to directly compare multi-domain power in the prior art are effectively solved. This achieves comprehensive perception of in-band signals, out-of-band interference, and thermal noise. Based on this, the theoretical gain adjustment amount is determined according to the aligned signal strength at the analog-to-digital converter output, and the allocation of analog and digital gain is jointly decided by combining multi-domain information, thereby providing a strong basis for gain allocation decision and improving the reliability of gain allocation.

[0007] Secondly, embodiments of this application provide a gain control device applied to a terminal, the device comprising: The RSSI acquisition module is used to acquire the received signal strength indications of multiple different observation nodes in the receiver. The observation nodes are located after the analog front end, the analog-to-digital converter output, and the baseband filter, respectively. The alignment module is used to align the received signal strength indication to a unified reference frame based on the link gain corresponding to each observation node. The adjustment amount determination module is used to determine the theoretical gain adjustment amount that the receiver needs to achieve based on the received signal strength indication at the output of the aligned analog-to-digital converter. The gain determination module is used to determine the analog gain and digital gain to be configured based on the received signal strength indications after alignment and the theoretical gain adjustment amount. A gain control module is used to configure the analog gain and the digital gain to the corresponding devices respectively, so as to perform gain control using the analog gain and the digital gain in the next gain control cycle.

[0008] Thirdly, embodiments of this application provide an electronic device, including a processor and a memory, wherein the memory stores computer-readable instructions, and when the computer-readable instructions are executed by the processor, the steps of the method provided in the first aspect above are performed.

[0009] Fourthly, embodiments of this application provide a computer-readable storage medium having a computer program stored thereon, which, when executed by a processor, performs the steps of the method provided in the first aspect above.

[0010] Fifthly, embodiments of this application provide a computer program product, including computer program instructions, which, when read and executed by a processor, perform the steps of the method provided in the first aspect above.

[0011] Other features and advantages of this application will be set forth in the following description and will be apparent in part from the description or may be learned by practicing embodiments of this application. The objectives and other advantages of this application may be realized and obtained by means of the structures particularly pointed out in the written description, claims, and drawings. Attached Figure Description

[0012] To more clearly illustrate the technical solutions of the embodiments of this application, the accompanying drawings used in the embodiments of this application will be briefly introduced below. It should be understood that the following drawings only show some embodiments of this application and should not be regarded as a limitation of the scope. For those skilled in the art, other related drawings can be obtained based on these drawings without creative effort.

[0013] Figure 1 A flowchart of a gain control method provided in an embodiment of this application; Figure 2 A structural block diagram of a gain control device provided in an embodiment of this application; Figure 3 This is a schematic diagram of the structure of an electronic device for performing a gain control method, provided as an embodiment of this application. Detailed Implementation

[0014] The technical solutions in the embodiments of this application will be clearly and completely described below with reference to the accompanying drawings.

[0015] It should be noted that the terms "system" and "network" in the embodiments of this invention can be used interchangeably. "Multiple" refers to two or more; therefore, in the embodiments of this invention, "multiple" can also be understood as "at least two". "And / or" describes the relationship between related objects, indicating that three relationships can exist. For example, A and / or B can represent: A existing alone, A and B existing simultaneously, and B existing alone. Additionally, the character " / ", unless otherwise specified, generally indicates that the preceding and following related objects have an "or" relationship.

[0016] It should also be noted that all actions involving the acquisition of signals, information, or data in this application are carried out in compliance with the relevant data protection laws and policies of the country where the application is located, and with the authorization granted by the owner of the relevant device.

[0017] This application provides a gain control method that simultaneously acquires received signal strength indications at multiple observation nodes—namely, the analog front-end, the analog-to-digital converter output, and the baseband filter—and aligns them to a unified reference frame. This effectively solves the problems of incomplete single-point detection information and the inability to directly compare multi-domain power in existing technologies, achieving comprehensive perception of in-band signals, out-of-band interference, and thermal noise. Based on this, the theoretical gain adjustment amount is determined according to the signal strength at the aligned analog-to-digital converter output, and the allocation of analog and digital gain is jointly decided by combining multi-domain information, thereby providing a strong basis for gain allocation decisions and improving the reliability of gain allocation.

[0018] Please refer to Figure 1 , Figure 1 A flowchart of a gain control method provided in this application embodiment, the method being applied to a terminal, includes the following steps: Step S110: Obtain the received signal strength indications from multiple different observation nodes in the receiver.

[0019] The Received Signal Strength Indication (RSSI) is a metric used to characterize the signal power at a specific observation node in the receiver, expressed as a power value in dBm or dBFS. In this scheme, RSSI does not refer to a specific measurement defined in a particular standard protocol, but rather to the signal power measurement at different nodes in the receive link.

[0020] The observation nodes are located after the analog front-end, the analog-to-digital converter output, and the baseband filter. Understandingly, an observation node refers to the specific physical location in the receiving link used to extract the RSSI. Different observation nodes are located after different gain stages in the link, and the RSSI measured by each node reflects the signal power state after the cumulative effect of all gain stages before that node.

[0021] In practical implementation, the terminal receiver sets up multiple RSSI extraction points at different locations on its receiving link to acquire the RSSI values ​​of each observation node under the current state. Specifically, this embodiment sets up at least three observation nodes: the first observation node is located at the analog front end and is used to acquire the analog RSSI, which reflects the total air interface power, including all received energy including in-band signal, out-of-band interference, and thermal noise; the second observation node is located at the digital output of the analog-to-digital converter (ADC) and is used to acquire the broadband RSSI, which reflects the total power of the signal within the ADC Nyquist bandwidth after passing through the analog amplification link and analog low-pass filter; the third observation node is located after the baseband filter and is used to acquire the narrowband RSSI, which reflects the effective signal power within the target bandwidth after filtering and downsampling. The RSSI of each observation node can be acquired through hardware detection circuits, digital domain power statistics, etc., and its measurement period matches the execution period of automatic gain control.

[0022] Step S120: Align the received signal strength indicators to a unified reference frame according to the link gain of each observation node.

[0023] In this context, aligning can be understood as converting RSSIs from different observation nodes according to the gain differences of each node relative to a unified reference plane, so that RSSIs that were originally at different power reference planes can be transformed to the same reference plane for comparison or calculation. Since different observation nodes are located at different positions on the link and have experienced different gain levels, without aligning, the RSSIs would not be comparable.

[0024] In other words, because each observation node is located at a different gain level in the receiving link, the RSSIs at each node are actually on different power reference planes, making direct comparison or joint calculation impossible. Therefore, the terminal performs equalization processing on each acquired RSSI based on the currently active link gain state. Equalization means that, based on the signal gain experienced from the antenna port to each observation node (including the positive gain contributed by the amplifier, the negative gain contributed by the attenuator, and the insertion loss of passive devices), each RSSI is converted to an equivalent power value under the same reference plane. The choice of reference frame does not affect the comparison logic of the equalization results; it can be selected as the antenna port equivalent input power reference frame, the ADC input equivalent power reference frame, or other unified reference plane, depending on the system design requirements. After equalization processing, the RSSIs, which were originally on different orders of magnitude due to link gain differences, are transformed to the same reference frame, becoming comparable and laying the foundation for joint decision-making in subsequent steps.

[0025] Step S130: Determine the theoretical gain adjustment amount that the receiver needs to achieve based on the received signal strength indication at the output of the aligned analog-to-digital converter.

[0026] The terminal calculates the total gain adjustment required for the current receiving link based on the deviation between the aligned ADC output bandwidth RSSI and the preset target power. This preset target power is pre-set based on the ADC's optimal dynamic range utilization and the quantization noise margin of the baseband processing. Specifically, when the aligned bandwidth RSSI is lower than the preset target power, it indicates that the current signal power is weak and the total gain needs to be increased; when the bandwidth RSSI is higher than the preset target power, it indicates that the current signal power is strong and the total gain needs to be decreased. This deviation is the theoretical gain adjustment, representing the magnitude of gain adjustment required for the entire receiving link to reach the target signal power at the ADC output. This theoretical gain adjustment is an intermediate calculation and not the final gain value directly configured in the hardware; rather, it serves as the basis for subsequent analog and digital domain gain allocation.

[0027] Step S140: Determine the analog gain and digital gain to be configured based on the received signal strength indications after alignment and the theoretical gain adjustment.

[0028] The theoretical gain adjustment obtained above is a total constraint. Combining the receiving environment information reflected by multiple RSSIs after alignment, the total amount is allocated between the analog and digital domains to determine the final analog gain value configured to the analog front end and the digital compensation value configured to the digital domain.

[0029] Regarding the determination of analog gain, the terminal uses the comparison between the aligned analog front-end RSSI and the broadband RSSI of the ADC output to perceive the current interference scenario. The principle is that when strong out-of-band blocking or interference signals are present, the relationship between the analog front-end RSSI and the ADC broadband RSSI deviates from the normal relationship under interference-free conditions. Based on the degree of deviation, the terminal can determine whether the current receiving environment is a strong interference scenario or a clean scenario, and thus select an appropriate analog gain allocation strategy. Different allocation strategies reflect different design trade-offs: in a strong interference environment, priority is given to reducing analog gain to improve receiver linearity and avoid saturation of some analog modules before the analog low-pass filter; in a clean environment, priority is given to increasing analog gain to optimize the system noise figure. After determining the allocation strategy, the terminal combines the theoretical gain adjustment amount to query the corresponding analog gain configuration value under that strategy. Since the gain of analog front-end devices is usually a discrete step value, the selected analog gain value should be the achievable value closest to the theoretical requirement under the condition of satisfying the strategy constraints.

[0030] Regarding the determination of digital gain, after determining the analog gain, the terminal uses the remaining deviation between the theoretical gain adjustment and the analog gain as the basic quantity that needs to be compensated in the digital domain. Based on this, the terminal can further introduce the difference between the wideband RSSI at the aligned ADC output and the narrowband RSSI after the baseband filter to correct this basic quantity. The significance of introducing this difference lies in the fact that factors such as the frequency response characteristics of the baseband filter (including passband roll-off loss), the filter's suppression effect on out-of-band interference, and the processing gain brought by downsampling can all cause the power relationship before and after the baseband filter to deviate from the ideal state. By including this difference in the calculation of digital gain, these link mismatch factors can be uniformly compensated, ensuring the constant power of the baseband output signal. The final determined digital gain value is the net compensation amount after considering the above factors.

[0031] Step S150: Configure the analog gain and digital gain to the corresponding devices respectively, so as to use the analog gain and digital gain for gain control in the next gain control cycle.

[0032] The terminal sends the determined analog gain value to each adjustable device in the analog front-end (including but not limited to LNA (Low Noise Amplifier), VGA (Variable Gain Amplifier), attenuators, etc.), and sends the digital gain value to the gain compensation module in the digital domain. After the gain configuration is completed, the receiving link uses the newly configured analog and digital gains for signal reception and processing in the next gain control cycle, thereby realizing closed-loop automatic gain control. After each round of the above steps is completed, the terminal starts the next round of RSSI measurement and gain calculation cycle, realizing continuous tracking and adaptive adjustment to the dynamically changing receiving environment.

[0033] In some implementations, when configuring analog gain and digital gain, the analog gain can be configured to the analog front end first, and after waiting for a preset time, the digital gain can be configured to the digital gain compensation module.

[0034] The preset duration refers to the time required from the moment the analog gain configuration takes effect until the moment the digital gain can be safely configured and taken effect. The purpose of this duration is to provide sufficient setup and stabilization time for the gain switching of each stage of the analog front-end devices, ensuring that the output signal of the analog link is fully stabilized in the new gain state before the digital gain is introduced. This duration can be preset to a fixed value (such as 20μs, 50μs, or 100μs) or dynamically calculated based on the current adjustment range of the analog gain (the larger the adjustment range, the longer the stabilization time required).

[0035] To overcome the above problems, this implementation introduces a necessary timing interval between the configuration of analog gain and digital gain, as specifically implemented as follows: After determining the analog gain, the terminal first performs the gain configuration operation for the analog front-end. Specifically, the terminal sends the configuration words for each level of the analog gain to each adjustable device in the analog front-end through the control interface. The configuration operation should follow the order of the devices at each level. Based on the degree of influence of each device on signal quality, front-end devices such as LNAs and attenuators should be configured first, followed by the VGA. However, the overall principle is to complete the configuration writing operation of all analog devices in a short period of time.

[0036] After the analog gain configuration command is issued, each analog device begins to switch from its current gain state to the new gain state. At this time, the output signal of the analog link enters a transient period, and both the signal quality and amplitude are in an uncertain state.

[0037] After the analog gain is configured, the terminal does not immediately configure the digital gain, but instead inserts a waiting period, i.e., a preset duration. The purpose of this preset duration is to allow the various stages of the analog front-end devices sufficient time to complete the entire transient process of gain switching, so that the output signal can return to a stable state.

[0038] The specific value of the preset duration can be determined based on the following factors: In one implementation, the preset duration is a pre-fixed empirical value. This empirical value is determined based on the maximum gain switching settling time given in the datasheet of the device used in the receiver front-end, with an additional margin added. For example, for a receiver front-end using an LNA and VGA, the preset duration can be set to a fixed value between 20μs and 100μs, which is sufficient to cover the gain switching settling time of most commercial devices.

[0039] In another implementation, the preset duration is dynamically calculated based on the adjustment magnitude of the current analog gain relative to the currently effective value. A larger adjustment magnitude results in greater changes in the bias states of each device level, and a longer stabilization time. For example, the terminal can determine the preset duration using the following formula: T_wait = T_base + k × |G_analog - G_current|, where T_base is the minimum waiting time (e.g., 10 μs), k is a scaling factor related to device characteristics, G_analog represents the analog gain to be configured, G_current represents the currently effective total analog gain, and |G_analog - G_current| is the magnitude of the current analog gain adjustment. This dynamic calculation method can minimize the waiting time and improve AGC response speed while ensuring sufficient signal stability.

[0040] In another implementation, the terminal determines whether it has entered a stable state by monitoring the power detection signal output by the analog link during the waiting period. When the fluctuation of the power detection signal is less than a preset threshold, it is considered stable, and the waiting can be ended in advance and the next step can be entered.

[0041] After a preset waiting period, the terminal confirms that the output signal of the analog link has reached a stable state, and then performs digital gain configuration. The terminal converts the determined digital gain value into a control word for the digital gain compensation module and writes it to the module's configuration register through the digital control interface. Upon receiving the new configuration word, the digital gain compensation module begins to use the new gain coefficient to amplitude scale the baseband signal at the next clock edge or the next data symbol boundary.

[0042] Because the digital gain compensation module operates on digital logic, its configuration process does not exhibit the transient response of analog circuits. Gain coefficient switching can be completed within a single clock cycle, and the switching process does not produce overshoot or DC drift phenomena found in the analog domain. Therefore, configuring the digital gain under the premise that the analog link is already stable ensures that the digital gain compensation module only processes valid and stable baseband signals and does not amplify any transient abnormal components.

[0043] In some implementations, the terminal may further employ enhancement measures to optimize gain switching quality. For example, during a preset waiting period, the terminal may control the baseband processing unit to suspend processing of the received signal (i.e., disable the baseband input data gating gate), and then resume baseband processing after the digital gain configuration is complete. This measure prevents invalid data sampled by the ADC and written to the baseband buffer during the transient phase of the analog link from being used by subsequent processing units.

[0044] After the digital gain is configured, the terminal can instruct the baseband filter to reset its internal state variables, that is, clear the filter's historical data register to ensure that the filter starts accumulating from zero in the new gain state, avoiding additional transient response caused by the mismatch between the filter's historical state and the current signal amplitude.

[0045] With the above configuration, the transient process of the analog link is completed and dissipates before the digital gain is intervened. The digital gain always operates under stable signal conditions, avoiding the amplification of transient signals and adverse effects on baseband processing. Secondly, the output signal quality of the receiver is guaranteed during gain switching, and the synchronization tracking loop and channel estimation module are not interfered with by gain switching.

[0046] In the above implementation process, by simultaneously acquiring the received signal strength indication at multiple observation nodes, namely the analog front-end, the analog-to-digital converter output, and the baseband filter, and aligning it to a unified reference frame, the problems of incomplete single-point detection information and the inability to directly compare multi-domain power in the prior art are effectively solved. This achieves comprehensive perception of in-band signals, out-of-band interference, and thermal noise. Based on this, the theoretical gain adjustment amount is determined according to the aligned signal strength at the analog-to-digital converter output, and the allocation of analog and digital gain is jointly decided by combining multi-domain information, thereby providing a strong basis for gain allocation decision and improving the reliability of gain allocation.

[0047] Based on the above embodiments, in the above method of aligning the received signal strength indications to a unified reference system, the received signal strength indication of each observation node can be subtracted from the link gain of the corresponding observation node to obtain the strength deviation of each observation node. The strength deviation of each observation node is then added to the reference gain of the unified reference system to obtain the aligned received signal strength indication of each observation node.

[0048] Link gain refers to the algebraic sum of the gains of all active and passive devices that the signal passes through from the antenna port to a certain observation node.

[0049] Intensity bias refers to the equivalent power value obtained by converting the RSSI measured at a certain observation node to the antenna port. Its physical meaning is "how much power needs to be input to the antenna port to make the observation node exhibit the currently measured signal strength". Numerically, intensity bias equals the observation node's RSSI minus the link gain corresponding to that node. When the RSSIs of multiple observation nodes are converted into their respective intensity biases, they are all on the same reference plane (antenna port), thus achieving comparability.

[0050] Reference gain refers to the offset of the unified reference frame relative to the antenna port reference plane, expressed in dB. Depending on the selected reference frame, the reference gain takes different fixed values: when the antenna port equivalent input power reference frame is selected as the unified reference frame, the reference gain is 0 dB; when the ADC input equivalent power reference frame is selected as the unified reference frame, the reference gain is equal to the link gain from the antenna port to the ADC input; when the unified power reference frame under the current analog total gain is selected as the unified reference frame, the reference gain is 0 dB and all link gains are set to 0 dB.

[0051] After completing the RSSI measurements at each observation node, the terminal needs to perform a unified alignment process on the RSSIs located on different power reference planes. This implementation breaks down the alignment process into several calculation stages to ensure that the RSSIs of each observation node are ultimately converted to the selected unified reference frame.

[0052] In the first stage, the terminal acquires the currently effective link gain configuration information. Since each observation node is located at a different position on the receiving link, each observation node corresponds to a different link gain value from the antenna port. For the analog front-end observation node, its link gain G1 is the algebraic sum of the gains of each stage of devices traversed from the antenna port to the analog node, specifically including the LNA gain and the insertion loss or attenuation of filters and attenuators that may exist along the path. For the ADC output observation node, its link gain G2 is the algebraic sum of the gains of all analog links from the antenna port to the ADC output, i.e., the currently effective total analog front-end gain. For the observation node after the baseband filter, its link gain G3 is the algebraic sum of all gains from the antenna port to the baseband filter output, including not only the total analog front-end gain but also the fixed gains of digital channels such as digital downconversion and downsampling. The above link gain values ​​are read in real-time from the current gain configuration register and precisely corrected by the calibration parameters stored during the factory calibration phase.

[0053] In the second stage, the terminal uses the aforementioned link gain to recalculate the original RSSI of each observation node, calculating the corresponding intensity deviation for each node. Specifically, for the original RSSI of the simulated front-end observation node (denoted as RSSI1), the link gain G1 corresponding to that node is subtracted, resulting in the intensity deviation D1 = RSSI1 - G1. For the original RSSI of the ADC output observation node (denoted as RSSI2), the link gain G2 corresponding to that node is subtracted, resulting in the intensity deviation D2 = RSSI2 - G2. For the original RSSI of the observation node after the baseband filter (denoted as RSSI3), the link gain G3 corresponding to that node is subtracted, resulting in the intensity deviation D3 = RSSI3 - G3. After this stage of processing, each intensity deviation D1, D2, and D3 represents the equivalent value of the power measured at each observation node after being converted to the antenna port. All three are now under the same reference plane and are physically comparable.

[0054] In the third stage, the terminal determines the corresponding reference gain G_ref based on the unified reference frame type selected in the system design. If the antenna port equivalent input power reference frame is used, the reference gain G_ref = 0dB. In this case, the aligned RSSIs are the intensity deviations calculated in the first stage, requiring no additional translation. If the ADC input equivalent power reference frame is used, the reference gain G_ref equals the current link gain from the antenna port to the ADC input (i.e., G2 minus the ADC's own fixed gain). In this case, all intensity deviations need to be translated to the ADC input reference plane. If the unified power reference frame under the current simulation total gain is used, the reference gain G_ref = 0dB and the link gain of each observation node is also taken as 0dB. In this case, the alignment process degenerates into no conversion, and the original RSSIs of each observation node are directly used as the alignment result.

[0055] After determining the reference gain G_ref, the terminal adds the intensity deviation of each observation node to G_ref to obtain the final aligned RSSI values. Specifically, the aligned analog front-end RSSI is RSSI1_align = D1 + G_ref, the aligned ADC output RSSI is RSSI2_align = D2 + G_ref, and the aligned baseband filter RSSI is RSSI3_align = D3 + G_ref. After these three stages of processing, the three original RSSIs, which were originally located on different power reference planes due to being behind different gain stages, are finally unified and converted to the same reference frame.

[0056] In the above implementation process, by subtracting the link gain from the antenna port to each observation node from the received signal strength indication of each observation node, and then uniformly adding the reference gain of the reference frame, the analog domain RSSI, ADC broadband RSSI, and baseband narrowband RSSI, which were originally located on different power reference planes, had different physical meanings, and could not be directly compared, can be accurately converted to the same reference frame for joint calculation. This homogenization process fundamentally eliminates the interference of link gain differences on the RSSI values ​​of each domain, so that subsequent interference state determination and digital gain compensation are completed on a unified physical reference, avoiding decision errors and accumulated errors caused by inconsistencies in the reference frame, and significantly improving the accuracy of gain control decisions and the consistency of link power adjustment.

[0057] In some implementations, the unified reference frame can be any one of the antenna port equivalent input power reference frame, the analog-to-digital converter input equivalent power reference frame, and the unified power reference frame under the current analog total gain.

[0058] The antenna port equivalent input power reference frame is a reference frame based on the input power at the receiver antenna port. Under this reference frame, the physical meaning of RSSI is the equivalent received power referred to the antenna port, reflecting the actual signal strength at the air interface. The reference gain of this reference frame is defined as 0 dB.

[0059] The equivalent power reference frame (RSSI) at the ADC input is a reference frame based on the signal power at the input port of the analog-to-digital converter (ADC). Under this reference frame, RSSI physically represents the equivalent signal power referred to the ADC input, directly reflecting the amplitude of the input signal actually sensed by the ADC. This reference frame is related to the receiver's internal gain state.

[0060] The unified power reference frame under the current simulated total gain is based on the currently effective simulated front-end total gain. This means that no additional calculations are performed; subsequent comparisons are directly based on the actual power surface at which each observation node is located. This reference frame is suitable for scenarios where the absolute power at the antenna port is not required, and only relative comparisons are needed.

[0061] The basic principle of Laching is as follows: In the receiver link, different observation nodes are located after different gain stages. Let the signal gain from the antenna port to a certain observation node be G_node (in dB), which is the algebraic sum of the positive gain contributed by each stage of amplifiers along the path, the negative gain contributed by attenuators, and the insertion loss of passive devices. If the original RSSI measured at the observation node is P_node, then the equivalent power referred to the antenna port is P_node - G_node.

[0062] Since each observation node corresponds to a different G_node, directly comparing each P_node will not reflect the true signal relationship over the air interface. The essence of alignment processing is to recalculate each P_node to the same reference plane based on the G_node of each observation node, so that the recalculated power values ​​are on the same physical reference, thereby enabling meaningful joint calculations and decisions.

[0063] For the sake of consistency, the Lasimilator formula is defined as follows: RSSI_align=P_node-G_node+G_ref; Where G_ref is the reference gain (in dB) corresponding to the unified reference frame, and its value is determined by the selected reference frame type. RSSI_align is the power value after alignment. The physical meaning of this formula is: first, the power at the observation point is converted to the antenna aperture (subtracting G_node), and then the entire power is translated to the target reference plane according to the reference frame requirements (adding G_ref).

[0064] The following section introduces different implementation methods for homogenization under different references.

[0065] (1) Antenna port equivalent input power reference frame.

[0066] When the unified reference frame is chosen as the antenna port equivalent input power reference frame, G_ref=0dB. The equivalent input power of the antenna port is directly obtained by subtracting the link gain from the antenna port to each observation node from the RSSI of each observation node.

[0067] For an observation node located at the analog front end, its RSSI is denoted as P_ana. Let the link gain from the antenna port to this node be G_ana. Then the equalized RSSI value for this node is: ANA_RSSI_align=P_ana-G_ana; This value is the equivalent value of the signal power at the observation node converted to the antenna port, reflecting the total air interface power level sensed by the analog front-end node.

[0068] For an observation node located at the ADC output, its RSSI is denoted as P_wb. Let the link gain from the antenna port to the ADC output be G_wb (i.e., the total gain of the current analog front-end). Then, the equalized RSSI value for this node is: WB_RSSI_align=P_wb-G_wb; This value reflects the equivalent input power required at the antenna port to make the ADC output present the current power level.

[0069] For an observation node located after the baseband filter, its RSSI is denoted as P_nb. Let the link gain from the antenna port to this node be G_nb (including analog front-end gain and fixed digital channel gain). Then, the equalized RSSI value for this node is: NB_RSSI_align=P_nb-G_nb; This value reflects the equivalent input power required at the antenna port to achieve the current power level after the baseband filter.

[0070] The advantage of this reference frame is that its physical meaning is clear. Each RSSI after alignment directly represents the equivalent power at the antenna port, which is convenient for comparison with the air interface standard. Moreover, the judgment result is independent of the receiver's internal gain state.

[0071] (2) Equivalent power reference frame at the input of analog-to-digital converter.

[0072] When the unified reference frame is chosen as the equivalent power reference frame for the ADC input, G_ref = G_wb, which is the gain from the antenna port to the ADC input. In this case, the RSSI values ​​of all observation nodes after alignment are converted to the equivalent power of the ADC input.

[0073] For the observation node at the ADC output, the Lackey formula is: WB_RSSI_align=P_wb-G_wb+G_wb=P_wb; That is, the RSSI at the ADC output remains unchanged because the node itself is located at the ADC output, and the reference plane is the ADC input (the input and output of the ADC have a fixed gain relationship, and the power at the ADC output can be converted to its input).

[0074] For the simulated front-end observation node, the Lazie formula is: ANA_RSSI_align=P_ana-G_ana+G_wb; This value represents the equivalent power at the analog front-end node when referred to the ADC input.

[0075] For the observation node after the baseband filter, the Lackey formula is: NB_RSSI_align=P_nb-G_nb+G_wb; This value represents the equivalent value of the power after the baseband filter is referred to the ADC input.

[0076] The advantage of this reference system is that it uniformly converts each RSSI to the ADC input, making it easy to directly evaluate whether the ADC is in the optimal input amplitude range. This is convenient in implementations that require prioritizing the protection of the ADC from saturation.

[0077] (3) The unified power reference frame under the current simulation total gain.

[0078] When the unified reference frame is chosen as the unified power reference frame under the current total analog gain, G_ref=0dB and each observation node no longer subtracts its own link gain, that is, the Lazy formula degenerates into: RSSI_align=P_node; The RSSI at each observation node retains its original measurement value without any conversion. In this reference frame, Lackey formally means no gain conversion, but essentially, the power values ​​at each observation point remain on the same reference plane, i.e., a reference plane with the currently active total simulated gain as a unified benchmark. The relative relationships between the RSSIs directly reflect the power differences between the observation points.

[0079] This reference frame is suitable for the following scenarios: when it is not necessary to know the absolute power value at the antenna port or ADC input, but only to compare the relative power between each observation node (e.g., calculating the power difference between the analog front-end and the ADC broadband, or the power difference between the ADC broadband and the baseband narrowband), the original RSSI can be used directly for difference calculation without introducing conversion error. Since the common gain terms in each RSSI cancel each other out when making the difference, the difference result is completely equivalent to whether it is converted to the antenna port.

[0080] Although the three reference frames mentioned above provide different G_ref values ​​and equalization results, they are equivalent for the core logic of this scheme. This is because both the comparison between the analog front-end and the ADC bandwidth (used for interference detection) and the difference between the ADC bandwidth and the baseband narrowband (used for digital gain compensation) are essentially based on the difference between the equalized RSSI values. When the same G_ref is added to or subtracted from all the components involved in the calculation, the difference remains unchanged. Therefore, regardless of the reference frame chosen, the analog gain allocation decision and the digital gain calculation conclusion remain consistent and will not produce substantial differences due to different reference frame selections.

[0081] The choice of reference frame depends on the convenience of hardware calibration and design preferences of the terminal. For example, if the terminal has already established accurate calibration of the antenna port power in factory calibration, the antenna port equivalent input power reference frame is preferred; if the terminal wants to simplify the equalization calculation, the unified power reference frame under the current analog total gain is preferred, and the original RSSI is used directly for difference calculation. The terminal can flexibly configure the value of G_ref according to actual needs without affecting the implementation of the core scheme of this invention.

[0082] Regardless of the reference frame used, the key to alignment accuracy lies in the accuracy of the link gain G_node corresponding to each observation node. During factory calibration, the terminal needs to measure and store the following information: the actual gain values ​​(not nominal values) of each amplifier stage at different gain levels, the actual attenuation of various attenuators, the insertion loss of passive components, and the absolute power level corresponding to the full-scale ADC. These calibration parameters can be stored in the terminal's non-volatile memory for the AGC algorithm to access in real time upon power-up or gain configuration changes. When the gain configuration of a component in the link changes, the G_node of each observation node must be updated synchronously to ensure that the alignment result always reflects the true gain state of the current link.

[0083] Based on the above embodiments, in determining the theoretical gain adjustment amount, the deviation between the received signal strength indication at the output of the aligned analog-to-digital converter and the preset target power can be obtained. Then, the deviation is smoothed by a first-order infinite impulse response low-pass filter to obtain the processed deviation amount. Based on the processed deviation amount and the reference gain of the unified reference system, the theoretical gain adjustment amount that the receiver needs to achieve is determined.

[0084] The deviation refers to the difference between the ADC output bandwidth RSSI after alignment and the preset target power, reflecting the degree to which the current received signal power deviates from the ideal target. A positive deviation indicates that the signal power is lower than the target (gain needs to be increased), while a negative deviation indicates that the signal power is higher than the target (gain needs to be decreased).

[0085] The preset target power refers to the signal power level that the ADC output is expected to reach. Its value is preset based on the optimal dynamic range utilization of the ADC and the quantization noise margin of the baseband signal processing. It is usually set to the value after the ADC full-scale power is backed down by a certain margin.

[0086] The first-order infinite impulse response (IIR) low-pass filter is a recursive digital filter whose current output depends on the weighted sum of the current input and the output at the previous time step. It features simple structure, low computational cost, and adjustable smoothing effect, making it suitable for smoothing in AGC systems with high real-time requirements.

[0087] After completing the alignment process for the received signal indication strengths, the terminal obtains the aligned RSSI of the ADC output, denoted as WB_RSSI_align. Simultaneously, the terminal reads the preset target power, denoted as P_target. The value of P_target is predetermined based on the ADC's full-scale range and the optimal operating range of the baseband processing. In this embodiment, P_target is preferably set to the power value corresponding to a 12dB~18dB power backoff from the ADC's full-scale range. This setting aims to simultaneously ensure sufficient signal peak margin (preventing ADC saturation due to large signals) and adequate quantization signal-to-noise ratio (ensuring signal quality for small signals).

[0088] The terminal calculates the difference between WB_RSSI_align and P_target to obtain the raw deviation Δ_raw: Δ_raw=P_target—WB_RSSI_align; The physical meaning of this raw deviation is: the gain adjustment required for the entire receiving link to achieve the target signal power at the ADC output. When Δ_raw > 0, it indicates that the current received power is lower than the target, and the total gain needs to be increased; when Δ_raw < 0, it indicates that the current received power is higher than the target, and the total gain needs to be decreased; when Δ_raw = 0, it indicates that the current power is already at the target level, and no adjustment is needed.

[0089] It should be noted that the above deviation is determined solely based on the wideband RSSI at the ADC output, rather than a combined calculation of RSSI from multiple domains. The ADC output is located at the boundary between the analog and digital links, and its RSSI reflects the total signal power after amplification by the full analog gain, making it the most direct indicator of whether the ADC is operating within its optimal range. Using the RSSI at this node as the basis for overall gain adjustment most effectively ensures that the ADC does not enter saturation or undersampling states, while its measurement accuracy and response speed are superior to the narrowband RSSI after the baseband filter.

[0090] Due to factors such as fast fading of the wireless channel, measurement noise, and signal bursts, the raw deviation Δ_raw calculated between adjacent AGC cycles may fluctuate significantly. If Δ_raw from each cycle is directly used for gain configuration, it may lead to frequent and large-scale gain switching, causing sudden changes in the received signal, which in turn affects synchronization tracking, demodulation performance, and the overall stability of the receiver.

[0091] Therefore, the terminal performs first-order IIR low-pass filtering smoothing on the raw deviation. Let the current AGC cycle number be t, the raw deviation calculated in the current cycle be Δ_raw[t], and the smoothed deviation from the previous cycle be Δ_smooth[t-1]. Then, the smoothed deviation Δ_smooth[t] in the current cycle is determined by the following recursive formula: Δ_smooth[t]=α·Δ_raw[t]+(1-α)·Δ_smooth[t-1]; Where α is the smoothing coefficient, with a value range of (0,1], and is dimensionless. The value of α determines the trade-off between the filter's response speed and smoothness: when α is large (close to 1), the filter has a fast response speed and can quickly track changes in signal power, but its ability to suppress measurement noise is weak, and the gain trajectory may not be smooth enough; when α is small (close to 0), the filter has a good smoothing effect and a stable gain trajectory, but there is a lag in the response to power abrupt changes, and the convergence time is longer.

[0092] In this embodiment, the value of α can range from 0.125 to 0.25, which achieves a good balance between AGC response speed and gain smoothness. In specific implementations, α can be a fixed value or dynamically adjusted according to the receiving scenario. For example, when the terminal initially connects or wakes up from deep sleep, a larger α value (such as 0.5 or 1.0) can be used to achieve fast gain acquisition; during the steady-state tracking phase, a smaller α value is switched to obtain a smooth gain trajectory.

[0093] The first-order IIR filter described above needs to store the smoothing result Δ_smooth[t] of the current cycle into a register after each AGC cycle, as the historical value Δ_smooth[t-1] for the next cycle. If the filter state is lost (e.g., due to power failure and reset), the initial state can be set to 0, and the original deviation can be directly used as the initial smoothing value in the first AGC cycle by setting α to 1.

[0094] After obtaining the smoothed deviation Δ_smooth[t], the terminal determines the theoretical gain adjustment G_target that the receiver needs to achieve.

[0095] When the unified reference frame is selected as the antenna port equivalent input power reference frame (G_ref=0dB), the theoretical gain adjustment is the smoothed deviation itself, i.e., G_target=Δ_smooth[t]. This value represents the gain adjustment required at the antenna port equivalent level for the entire receiver link.

[0096] When the unified reference frame is selected as the equivalent power reference frame of the ADC input (G_ref=G_adc) or the unified power reference frame under the current analog total gain (G_ref=0dB and not converted), the theoretical gain adjustment amount still needs to be aligned with the reference frame's base gain.

[0097] In general, the theoretical gain adjustment is determined by the following formula: G_target=Δ_smooth[t]+G_ref; Where G_ref is the reference gain (in dB) of the selected unified reference system, and its value is determined according to the selection of the reference system in step S120. The physical meaning of this formula is: to extend the smoothed deviation from the current reference system to the reference plane of the unified reference system, ensuring that the calculation of analog gain and digital gain in subsequent steps are performed under the same reference reference.

[0098] It should be noted that G_target represents the total gain adjustment that the entire receiving link needs to achieve, and its specific unit is consistent with the reference frame used. This theoretical gain adjustment is not directly configured to the final gain value of the hardware, but is used as an input in step S140 for the subsequent joint allocation of analog and digital gain. The terminal passes G_target to the analog gain allocation and digital gain compensation calculation stage, where it is decomposed into executable analog gain configuration values ​​and digital domain compensation values ​​in subsequent steps. At the end of each AGC cycle, after the terminal completes the gain configuration according to step S150, it begins the RSSI measurement and gain calculation for the next cycle, thereby achieving continuous closed-loop tracking control.

[0099] In the above implementation process, firstly, the deviation between the broadband RSSI of the aligned ADC output and the target power is used as the basis for overall gain adjustment. This most directly reflects the deviation between the actual ADC input and the optimal operating range, ensuring that the ADC is neither saturated nor loses quantization accuracy. Secondly, a first-order IIR filter is used to smooth the cycle-by-cycle deviation, suppressing gain command fluctuations caused by fast channel fading and measurement noise, preventing sudden gain changes from impacting synchronous tracking and demodulation performance. Moreover, the IIR structure is simple, and the coefficients can be flexibly configured according to the scenario, taking into account both response speed and stability. Finally, the smoothed deviation is combined with the unified reference frame gain to determine the theoretical gain adjustment amount, ensuring dimensional consistency and providing accurate constraints for the subsequent joint allocation of analog and digital gains.

[0100] Based on the above embodiments, in determining the analog and digital gains to be configured, a target analog gain allocation table can be selected from multiple analog gain allocation tables according to the degree of difference between the received signal strength indication at the aligned analog front end and the received signal strength indication at the analog-to-digital converter output; then, the analog gain is determined according to the target analog gain allocation table and the theoretical gain adjustment amount; and the digital gain is determined according to the difference between the received signal strength indication at the aligned analog-to-digital converter output and the received signal strength indication after the baseband filter, the theoretical gain adjustment amount, and the analog gain.

[0101] The analog gain allocation table refers to a data structure pre-installed in the terminal, used to map the desired total gain to the specific gain configuration of each adjustable device in the analog front-end (including LNA, mixer, VGA, attenuator, etc.). Different allocation tables correspond to different gain allocation strategies, with different priorities for gain allocation to each level of device while ensuring the overall gain of the receiver. Multiple analog gain allocation tables are pre-stored in the terminal, including at least a linearity-priority allocation table and a noise figure-priority allocation table.

[0102] After determining the theoretical gain adjustment amount G_target, the terminal needs to allocate the total gain adjustment amount between the analog and digital domains. First, determine the gain value that should be configured for the analog front end.

[0103] The terminal calculates the difference between the aligned analog front-end RSSI (ANA_RSSI_align) and the aligned ADC output bandwidth RSSI (WB_RSSI_align), denoted as Δ_ana_wb: Δ_ana_wb=ANA_RSSI_align-WB_RSSI_align; The difference Δ_ana_wb, as mentioned earlier, directly reflects the degree of out-of-band interference. The physical principle behind this relationship is as follows: RSSI_ANA is taken from the analog front-end, which has a wide measurement bandwidth, encompassing all air interface energy, including in-band signals, out-of-band interference, and thermal noise; RSSI_WB is taken from the ADC output, where out-of-band interference components are suppressed to some extent after passing through various filters in the analog link. When both are aligned to the same reference frame for comparison, if there is no out-of-band interference, they should be approximately equal (the difference should be within the measurement error range, typically ±2dB); if strong out-of-band interference exists, ANA_RSSI_align is significantly greater than WB_RSSI_align, with a larger difference indicating stronger out-of-band blocking. This degree of difference can also be used to indicate the power change characteristics before and after analog front-end filtering.

[0104] The terminal selects one of several pre-stored analog gain allocation tables as the target analog gain allocation table for the current period based on the range of Δ_ana_wb. In some implementations, the interference state of the current receiving environment can be determined first based on the degree of difference between the received signal strength indication at the aligned analog front-end and the received signal strength indication at the analog-to-digital converter output. If the interference state is strong interference, a target analog gain allocation table with linearity priority is selected from the multiple analog gain allocation tables; if the interference state is no interference, a target analog gain allocation table with noise figure priority is selected from the multiple analog gain allocation tables.

[0105] Interference status refers to the classification of the interference level in the electromagnetic environment in which the terminal receiver is currently located, used to characterize whether there are significant out-of-band blocking or interference signals. In this embodiment, based on the value of Δ_ana_wb, the interference status is divided into at least two types: strong interference status and no interference status.

[0106] Strong interference conditions refer to the operating state of the receiving environment where there are out-of-band blocking or interference signals of sufficient strength to affect the linearity performance of the receiver. Under this condition, the main risks faced by the receiver are LNA saturation, mixer overload, or ADC overflow caused by strong signals, resulting in nonlinear distortion and preventing the useful signal from being demodulated properly.

[0107] Interference-free operation refers to a receiving environment free from significant out-of-band blocking or interference signals, where the air interface signal quality is relatively pure. In this state, the main challenge for the receiver is addressing the impact of the noise figure on receiver sensitivity under weak signal conditions, rather than nonlinear distortion.

[0108] The linearity-first strategy refers to the principle of prioritizing receiver linearity in gain allocation. This strategy ensures that strong interference signals are sufficiently attenuated before entering the nonlinear devices by appropriately reducing the analog front-end gain (e.g., selecting a low-gain LNA or increasing the attenuation of the RF attenuator). This avoids receiver saturation or intermodulation distortion caused by strong signals and ensures that useful signals can still be received normally under interference conditions.

[0109] The noise figure priority strategy refers to the principle of prioritizing the allocation of gain to ensure the receiver's optimal noise figure. This strategy maximizes the analog front-end gain (e.g., by selecting a high-gain LNA setting and minimizing attenuator insertion loss) to ensure that weak signals are sufficiently amplified at the link front-end, thereby reducing the cascaded noise figure of the entire receiving link, improving receiver sensitivity, and ensuring that useful signals can still be effectively extracted under weak signal conditions.

[0110] This implementation utilizes the difference Δ_ana_wb between the aligned analog front-end RSSI and the broadband RSSI at the ADC output to sense the interference state of the receiving environment. The physical principle of this determination method is as follows: In wireless communication receivers, the observation node at the analog front end is typically located after the LNA and before (or within) the RF filter or anti-aliasing filter. Its RSSI reflects all electromagnetic energy received by the antenna, including the target in-band signal, out-of-band interference signal, and thermal noise. The broadband RSSI at the ADC output, however, reflects the total signal power reaching the ADC after passing through the entire analog link (including filters at each stage). When filters exist in the analog link, out-of-band interference components are partially suppressed, resulting in a reduction in interference energy received by the ADC relative to the antenna port.

[0111] After aligning the two RSSI values ​​to the same reference frame, compare their differences: if there is no out-of-band interference in the receiving environment, the two RSSI values ​​should be statistically equal (the difference is within the measurement error range); if there is strong out-of-band interference, due to the suppression of out-of-band components by the analog filter, the aligned analog front-end RSSI will be significantly greater than the broadband RSSI at the ADC output. The larger the difference, the stronger the out-of-band interference.

[0112] Based on the above principle, the terminal can monitor the value of Δ_ana_wb to perceive the interference status of the receiving environment in real time, thereby providing a basis for the selection of subsequent gain allocation strategies.

[0113] The terminal compares the calculated Δ_ana_wb with a preset interference determination threshold to determine the interference state of the current receiving environment. In this embodiment, the interference determination threshold is set based on the theoretical value of Δ_ana_wb (0dB, considering that the measurement error is usually within ±2dB) in the interference-free state.

[0114] Specifically, the terminal sets a first threshold th0 (th0 is a positive value, for example, 6dB) as the threshold for determining a strong interference state. When Δ_ana_wb is greater than th0, the current receiving environment is determined to be a strong interference state, indicating the presence of out-of-band blocking or interference signals with sufficient strength to affect the receiver's linearity. It should be noted that the larger Δ_ana_wb is, the stronger the out-of-band interference, and the greater the challenge to the receiver's linearity.

[0115] When Δ_ana_wb is less than or equal to th0, the terminal further determines whether significant interference exists. The terminal sets a second threshold th1 (th1 is a value less than th0, for example, it can be -3dB or 0dB) as the threshold for determining an interference-free state. When Δ_ana_wb is less than th1, the current receiving environment is determined to be interference-free, indicating that there are no significant out-of-band blocking signals, and the receiver operates in a relatively clean electromagnetic environment. In this state, the noise figure becomes the main factor affecting receiving performance, and gain allocation should prioritize optimizing the noise figure.

[0116] The value of th1 is described as follows: In theory, Δ_ana_wb should be 0dB in the interference-free state. However, due to factors such as RSSI measurement errors, link gain calibration errors and thermal noise fluctuations, the actually calculated Δ_ana_wb will fluctuate to a certain extent around 0dB. Therefore, setting th1 to a negative value slightly lower than 0dB (e.g., -3dB) or directly setting it to 0dB can ensure that interference is determined only when Δ_ana_wb really deviates from the normal range, and avoid misjudgment caused by normal measurement fluctuations.

[0117] It should be noted that in the above determination logic, when Δ_ana_wb is in the intermediate region between th1 and th0, the terminal can determine it as a moderate interference state. For the processing of the moderate interference state, the terminal can select a balanced allocation table, or classify it into either the strong interference state or the interference-free state according to design preferences, which is not limited in this paper. The above determination methods for three interference states are only exemplary divisions, and are not intended to limit the protection scope of the present invention.

[0118] When the terminal determines that the current receiving environment is in a strong interference state, that is, Δ_ana_wb>th0, an analog gain allocation table with priority on linearity is selected as the target analog gain allocation table.

[0119] In the linearity-priority allocation table, the allocation of analog gain follows the following principles: low-gain LNA gears are preferentially used to reduce the signal amplitude at the output end of the LNA, so as to avoid harmonic distortion caused by the LNA entering a nonlinear region due to strong signals; the attenuation of the radio frequency attenuator is preferentially increased, so that strong interference signals are fully attenuated before entering nonlinear devices such as mixers and VGAs; the maximum gain of VGA is appropriately limited to avoid saturation of strong signals in the post-stage amplification link.

[0120] The common objective of the above allocation principles is to ensure the linearity index of the receiver under strong interference conditions, so that when an out-of-band blocking signal exists, the receiver can still normally amplify and demodulate the useful signal without generating additional interference components due to nonlinear distortion. Although this strategy will slightly degrade the noise figure of the receiver (the increased insertion loss of the front-end attenuator and the reduced LNA gain lead to an increase in the proportion of noise contribution from the post-stage), in strong interference scenarios, linearity is the main contradiction affecting reception performance, and sacrificing part of the noise figure in exchange for anti-blocking capability is acceptable.

[0121] When the terminal determines that the current receiving environment is in an interference-free state, that is, Δ_ana_wb<th1, an analog gain allocation table with priority on noise figure is selected as the target allocation table.

[0122] In the noise figure priority allocation table, the allocation of analog gain follows these principles: prioritize the use of high-gain LNA settings to maximize the amplification of weak signals at the very beginning of the link, thereby minimizing the noise contribution of subsequent circuits; minimize the insertion loss of attenuators to avoid unnecessary attenuation of useful signals in an interference-free environment; and fully utilize the VGA's gain range to amplify the signal to the ADC's optimal input range as much as possible while ensuring linearity margin.

[0123] The common goal of the above allocation principles is to achieve the optimal cascaded noise figure for the entire receiver link. According to Fries's formula, the overall noise figure of the receiver is mainly determined by the noise figure and gain of the first-stage LNA. Maximizing the LNA gain can effectively reduce the contribution of subsequent circuit stages to the overall noise figure. In a clean environment, there is no risk of saturation due to strong interference, so the useful signal can be fully amplified to improve receiver sensitivity, which is crucial for weak signal coverage scenarios such as cell edges.

[0124] When Δ_ana_wb is in a moderate interference state between th1 and th0, the terminal can select an equalization allocation table, whose gain allocation strategy strikes a trade-off between linearity and noise figure. In other implementations, the terminal can also classify the moderate interference state into a strong interference state (biased towards conservatism, prioritizing linearity) or an interference-free state (biased towards aggressiveness, prioritizing sensitivity) according to preset safety preferences. The specific classification can be flexibly set by the terminal according to the actual application scenario, and this document does not impose any restrictions.

[0125] In this embodiment, the determination of interference status and the selection of the allocation table are performed independently in each AGC cycle. Since Δ_ana_wb reflects the current interference level in real time, when the interference environment changes (e.g., the terminal moves from a strong interference environment in an urban area to a clean environment in the suburbs, or out-of-band blocking changes due to frequency switching), the terminal can automatically switch to the corresponding allocation table in subsequent AGC cycles. This achieves dynamic adaptation of the gain allocation strategy to the interference environment without manual intervention or pre-configuration. This dynamic adaptability allows the receiver to maintain optimal operating conditions in a constantly changing electromagnetic environment.

[0126] After selecting a target analog gain allocation table, the terminal uses the theoretical gain adjustment value G_target as the input index to query the corresponding analog gain configuration in the selected allocation table. Each allocation table contains the mapping relationship between the theoretical gain adjustment value and the configuration parameters of each stage of the analog front-end devices, which can be represented in the following form: For each possible theoretical gain adjustment value G_target (or a discretized G_target value with a certain step size), the allocation table records a corresponding set of device configuration parameters, including but not limited to: LNA gain level selection, RF attenuation setting, VGA gain code value, etc. The terminal can obtain the optimal configuration parameters for each level of analog device in the current scenario by looking up the table based on the theoretical gain adjustment value G_target. These device parameters together constitute an achievable total analog gain value, which is the analog gain determined in this step, denoted as G_analog (in dB).

[0127] In some implementations, since the gain levels of the devices in the analog front-end are typically discrete, the total analog gain value recorded in the allocation table may not be exactly equal to G_target, but rather the closest achievable value to G_target that can be actually configured. This deviation will be compensated for in the subsequent digital gain determination process. Furthermore, to avoid signal abrupt changes caused by excessively large single gain adjustments, the terminal should also constrain the single-step change between the gain value and the currently effective analog gain value to not exceed a preset maximum allowable step size when determining the analog gain from the table. If it exceeds this limit, the adjustment should be performed gradually over multiple cycles to reach the desired level.

[0128] Specifically, the target gain can be selected from the target analog gain allocation table, where the difference between the target gain and the theoretical gain adjustment is the smallest and the difference between the target gain and the currently effective analog total gain is within a preset maximum allowable adjustment step size, and the target gain is determined as the analog gain.

[0129] The preset maximum allowable adjustment step size refers to the maximum permissible change in analog gain relative to the currently active value within one AGC cycle, measured in dB. This step size limit restricts the magnitude of a single gain switch, preventing drastic changes in the received signal amplitude caused by large gain adjustments, thereby avoiding adverse effects on subsequent synchronization tracking, channel estimation, and demodulation performance. This step size limit is a preset fixed value or a configurable parameter, typically ranging from 6 dB to 12 dB.

[0130] The currently effective total analog gain refers to the total amount of analog gain that has been configured to the analog front-end and is actually effective before the start of the current AGC cycle, i.e., the analog gain value actually used by the receive link after the configuration was completed in the previous cycle. This value serves as a benchmark to determine whether the new gain to be selected this time will cause an excessively large gain change.

[0131] After selecting the target analog gain allocation table, the terminal needs to determine a final analog gain value from the multiple selectable gain values ​​recorded in the table. In this embodiment, the selection of the analog gain needs to simultaneously meet the following two constraints to ensure that the analog gain closely approximates the theoretical requirements in terms of accuracy and is smooth and controllable in terms of dynamic changes.

[0132] Constraint 1: Minimize the difference from the theoretical gain adjustment. The target analog gain allocation table is a mapping table indexed by the theoretical gain adjustment G_target. The table records the configuration parameters of each stage of the analog front-end devices under different G_target values, as well as the corresponding achievable total analog gain values. Typically, an allocation table contains dozens to hundreds of discrete gain values ​​and their configuration parameter entries. These discrete gain values ​​cover the full gain range required for normal receiver operation. However, since the achievable gain values ​​of the analog front-end are discrete rather than continuously adjustable, the total analog gain value recorded in the table is often not exactly equal to G_target, but rather distributed among several discrete values ​​around G_target. The terminal selects the value with the smallest absolute difference from G_target from these options, i.e., the point closest to G_target in the discrete value sequence.

[0133] By selecting the gain value with the smallest difference, the deviation between the analog domain and the theoretical requirement can be reduced to the greatest extent, thereby reducing the amount of residual compensation that the digital domain needs to bear and achieving a reasonable distribution of gain burden between the analog and digital domains.

[0134] Constraint 2: The difference between the target gain and the currently effective total analog gain must be within the preset maximum allowable adjustment step size per turn. Besides considering the approximation to the theoretical value, the terminal must also consider the smoothness of gain switching. If the difference between the selected target gain and the currently effective analog gain is too large, a single gain switch will cause a drastic jump in signal amplitude. This sudden change may cause transient responses in the receiving link, the charging and discharging process of the baseband filter, and consequently, abnormal changes in the amplitude and phase of the demodulation reference signal, severely affecting synchronous tracking and demodulation performance. Therefore, when selecting the target gain, the terminal must ensure that the absolute value of the difference between the newly selected gain value and the currently effective total analog gain does not exceed the preset maximum allowable adjustment step size ΔG_max per turn.

[0135] The two constraints mentioned above work together to ensure that the simulated gain is as close as possible to the theoretical requirement, while also guaranteeing smooth gain switching. When both constraints are satisfied, the selected gain value is the optimal target gain.

[0136] Specifically, the terminal iterates through all available total analog gain values ​​and calculates the absolute difference between each value and G_target. The terminal sorts all available values ​​in ascending order of this difference, prioritizing the value closest to G_target. The terminal obtains the currently active total analog gain value G_current and, following the above sorting order, verifies whether each available value meets the step size constraint. For the first available value that simultaneously meets both the minimum difference priority and the step size constraint, the terminal designates it as the target gain G_analog, i.e., the analog gain. The terminal extracts the configuration parameters of each device level corresponding to the target gain G_analog and uses them as the analog gain values ​​to be configured to the analog front-end in the current AGC cycle.

[0137] In practical applications, a special case may arise: the difference between the optional value with the smallest difference from G_target and G_current exceeds ΔG_max, while optional values ​​with slightly larger differences may also exceed ΔG_max. In other words, no optional value in the allocation table can simultaneously satisfy both of the above constraints. To address this situation, this implementation provides the following processing mechanism: When none of the optional values ​​sorted by difference from smallest to largest by the terminal satisfy the step size constraint (i.e., the difference between the gain value closest to G_target and G_current in the allocation table exceeds ΔG_max, and the differences of the other optional values ​​are even larger, making it even less likely to satisfy the step size constraint), the terminal abandons the optimization objective of "minimum difference" and instead selects the optional gain value whose difference with G_current is closest to ΔG_max (i.e., the largest change without exceeding the step size limit) as the target gain, and defers the remaining unrealized gain adjustment to subsequent AGC cycles to be completed gradually.

[0138] In the above scenario, the terminal performs the following operations: From all available values ​​in the allocation table, it filters out all candidate values ​​that satisfy |G_opt[k] - G_current| ≤ ΔG_max, where G_opt[k] represents the k-th gain value in the table. From these candidate values, it selects the gain value whose absolute difference from G_current is closest to ΔG_max, i.e., the farthest point achievable within the current allowed single-step change range. This gain value is the actual analog gain used in the current cycle. The terminal configures the device parameters corresponding to this gain value to the analog front-end and records the remaining deviation between the actual adjustment amount and G_target. This remaining deviation will be compensated in subsequent digital gain calculations or gradually eliminated in the next AGC cycle by readjusting the analog gain.

[0139] Through the above mechanism, even if the theoretical requirement differs greatly from the current state, the receiver can gradually approach the theoretical gain with controlled steps over multiple AGC cycles, effectively avoiding signal damage caused by a single large gain switch.

[0140] In this embodiment, the maximum allowable adjustment step size ΔG_max is not fixed; the terminal can dynamically adjust the value of ΔG_max according to the modulation scheme and signal-to-noise ratio of the currently received signal. For example: When the terminal is in the initial gain acquisition phase (such as when it has just been powered on or woken up from deep sleep), the receiver does not yet have a valid signal to demodulate and is not sensitive to signal abrupt changes caused by gain switching. At this time, a larger ΔG_max (such as 12dB or even larger) can be used to make the gain converge quickly to near the target value.

[0141] When the terminal is in the steady-state reception stage and is demodulating a high-modulation-order signal, the receiver has high requirements for the stability of the signal amplitude. At this time, a smaller ΔG_max (such as 3dB or 6dB) should be used to minimize the impact of gain switching on demodulation performance.

[0142] When the terminal is in a weak signal coverage area at the edge of the cell, the signal itself is already weak, and sudden gain changes may cause synchronization loss. In this case, it is advisable to use a smaller ΔG_max to ensure the smoothness of the gain trajectory.

[0143] By dynamically adapting the value of ΔG_max, the terminal can achieve a balance between fast convergence and stable tracking, further optimizing the receiver's gain control performance in different operating scenarios.

[0144] After completing the analog gain query, the terminal temporarily stores the device configuration word corresponding to the analog gain, awaiting subsequent configuration steps to send it to the hardware. This analog gain also serves as the input for digital gain calculation. After the analog gain is configured, the receiving link receives signals with the newly configured analog gain in the next AGC cycle. If the theoretical gain adjustment is not fully achieved due to step size constraints, the remaining deviation is compensated by digital gain or the analog gain is adjusted in subsequent AGC cycles until it finally converges to the theoretical target value.

[0145] After the analog gain G_analog is determined, the terminal further determines the digital gain G_digital to be configured in the digital domain. In this embodiment, the determination of the digital gain takes into account two factors: first, the residual deviation between the theoretical total gain adjustment and the analog gain; and second, the link mismatch reflected by the power change before and after the baseband filter.

[0146] Subtracting the analog gain G_analog from the theoretical gain adjustment G_target determined above, we obtain the residual deviation Δ_residual that cannot be fully realized in the analog domain: Δ_residual=G_target—G_analog; The reason for this residual bias is that the analog gain is limited by the discrete levels and allocation strategies of the front-end devices, and can usually only provide a gain that is close to, but not exactly equal to, the theoretical value. This residual bias needs to be compensated in the digital domain; otherwise, the total gain will not accurately reach the theoretically required value.

[0147] The terminal further calculates the difference between the aligned ADC output broadband RSSI (WB_RSSI_align) and the aligned baseband filter narrowband RSSI (NB_RSSI_align), denoted as Δ_wb_nb: Δ_wb_nb=WB_RSSI_align-NB_RSSI_align; The difference Δ_wb_nb represents the power change experienced by the signal from the ADC output to the baseband filter. This change stems from the combined effect of several factors: the roll-off characteristic of the baseband low-pass filter at the passband edge causes a certain amplitude attenuation of the effective signal within the passband (roll-off loss); the filter's suppression of out-of-band interference components reduces the total power; and the downsampling operation in digital downconversion introduces processing gain. These factors collectively lead to the difference between the ADC wideband RSSI and the baseband narrowband RSSI, and this difference varies with signal bandwidth, filter parameters, and downsampling rate.

[0148] This implementation directly incorporates the difference Δ_wb_nb into the calculation of the digital gain to achieve unified compensation for the aforementioned link mismatch factors. The logic is that regardless of the specific reason for the difference between the ADC broadband RSSI and the baseband narrowband RSSI, the digital gain should compensate for this difference in reverse order to keep the signal power output by the baseband filter constant. By including this difference in the digital gain, precise constant baseband power control can be achieved without separately modeling and calculating factors such as roll-off loss, out-of-band rejection, and downsampling gain.

[0149] The terminal combines the residual deviation compensation with the baseband power difference compensation, and determines the digital gain G_digital using the following formula: G_digital=Δ_residual+Δ_wb_nb=(G_target-G_analog)+(WB_RSSI_align-NB_RSSI_align); The physical meaning of this formula is that digital gain must not only compensate for the residual deviation that analog gain cannot precisely achieve, but also compensate for the power change before and after the baseband filter. Together, these two factors constitute the entire gain adjustment task that the digital domain needs to undertake. In practical implementation, digital gain can be achieved by amplitude scaling of the baseband signal using a complex multiplier, or by combining a shifter with a multiplier. The calculated digital gain can be positive or negative: a positive gain indicates that the digital domain needs to amplify the signal, while a negative gain indicates that attenuation is required.

[0150] In some implementations, the terminal can also set a safety limit range for the digital gain (typically -12dB to +18dB) to prevent digital domain overflow due to excessive gain or effective bit width loss due to insufficient gain. When the calculated digital gain exceeds the limit range, the terminal can feed back the excess portion to the analog gain allocation module, guiding the analog gain to adjust in a direction that reduces the burden on the digital gain in subsequent AGC cycles.

[0151] In this implementation, the determination of analog and digital gain is not independent, but rather a joint decision based on the same theoretical gain adjustment value G_target and unified, aligned multi-domain RSSI information. Their synergistic relationship is manifested in the following way: the theoretical gain adjustment value G_target is a total constraint, which is jointly satisfied by both analog and digital gains (i.e., the algebraic sum of G_analog and G_digital equals the algebraic sum of G_target and the power difference before and after the baseband filter). The allocation strategy of analog gain is determined by the interference scenario, while digital gain undertakes the dual function of compensating for residual bias and link mismatch. This reasonable division of labor ensures both the receiver's linearity in strong interference environments and the precise constancy of the baseband output power, achieving optimal overall receiver performance. After determining the analog and digital gains, the terminal configures and applies the two gain values ​​separately.

[0152] In the above implementation process, by using the difference between the aligned analog front-end RSSI and the broadband RSSI of the ADC output to sense the interference state and select the corresponding gain allocation table, the analog gain is adaptively allocated according to the interference environment. Under strong interference, linearity is prioritized, and under clean environment, noise figure is optimized. At the same time, by introducing the difference between the aligned ADC broadband RSSI and the baseband narrowband RSSI into the digital gain calculation, the link mismatch factors such as the baseband filter roll-off loss and downsampling processing gain are uniformly compensated, ensuring that the baseband output power is constant. Overall, the receiver linearity, noise figure and baseband power stability are comprehensively optimized.

[0153] Please refer to the above method embodiments. Figure 2 , Figure 2This is a structural block diagram of a gain control device 200 provided in an embodiment of this application. The device 200 may be a module, program segment, or code on an electronic device. It should be understood that the device 200 corresponds to the above method embodiment and is capable of performing the various steps involved in the method embodiment. The specific functions of the device 200 can be found in the description above. To avoid repetition, detailed descriptions are appropriately omitted here.

[0154] Optionally, the device 200 includes: RSSI acquisition module 210 is used to acquire the received signal strength indication of multiple different observation nodes in the receiver, wherein the observation nodes are located after the analog front end, the analog-to-digital converter output end and the baseband filter, respectively. The alignment module 220 is used to align the received signal strength indication to a unified reference frame according to the link gain corresponding to each observation node. The adjustment amount determination module 230 is used to determine the theoretical gain adjustment amount that the receiver needs to achieve based on the received signal strength indication at the output of the aligned analog-to-digital converter. The gain determination module 240 is used to determine the analog gain and digital gain to be configured based on the received signal strength indications after alignment and the theoretical gain adjustment amount. The gain control module 250 is used to configure the analog gain and the digital gain to the corresponding devices respectively, so as to perform gain control using the analog gain and the digital gain in the next gain control cycle.

[0155] Optionally, the gain determination module 240 is configured to select a target analog gain allocation table from multiple analog gain allocation tables based on the degree of difference between the received signal strength indication at the aligned analog front-end and the received signal strength indication at the analog-to-digital converter output; determine the analog gain based on the target analog gain allocation table and the theoretical gain adjustment; and determine the digital gain based on the difference between the received signal strength indication at the aligned analog-to-digital converter output and the received signal strength indication after the baseband filter, the theoretical gain adjustment, and the analog gain.

[0156] Optionally, the gain determination module 240 is used to determine the interference state of the current receiving environment based on the degree of difference between the received signal strength indication of the aligned analog front end and the received signal strength indication at the output of the analog-to-digital converter; if the interference state is a strong interference state, a target analog gain allocation table with linearity priority is selected from multiple analog gain allocation tables; if the interference state is a no-interference state, a target analog gain allocation table with noise figure priority is selected from multiple analog gain allocation tables.

[0157] Optionally, the gain determination module 240 is used to select a target gain from the target analog gain allocation table that has the smallest difference from the theoretical gain adjustment amount and whose difference from the currently effective analog total gain is within a preset single maximum allowable adjustment step size, and to determine the target gain as the analog gain.

[0158] Optionally, the aligning module 220 is used to subtract the link gain of the corresponding observation node from the received signal strength indication of each observation node to obtain the strength deviation of each observation node; and to add the strength deviation of each observation node to the reference gain of the unified reference system to obtain the received signal strength indication of each observation node after aligning.

[0159] Optionally, the adjustment amount determination module 230 is used to obtain the deviation between the received signal strength indication at the output of the aligned analog-to-digital converter and the preset target power; to smooth the deviation through a first-order infinite impulse response low-pass filter to obtain the processed deviation; and to determine the theoretical gain adjustment amount that the receiver needs to achieve based on the processed deviation and the reference gain of the unified reference system.

[0160] Optionally, the unified reference system can be any one of the following: the antenna port equivalent input power reference system, the analog-to-digital converter input terminal equivalent power reference system, and the unified power reference system under the current analog total gain.

[0161] Optionally, the gain control module 250 is used to configure the analog gain to the analog front end; and after waiting for a preset time, configure the digital gain to the digital gain compensation module.

[0162] It should be noted that those skilled in the art will clearly understand that, for the sake of convenience and brevity, the specific working process of the device described above can be referred to the corresponding process in the foregoing method embodiments, and will not be repeated here.

[0163] Please refer to Figure 3 , Figure 3This is a schematic diagram of an electronic device for performing a gain control method, provided in an embodiment of this application. The electronic device may include: at least one processor 310, such as a CPU; at least one communication interface 320; at least one memory 330; and at least one communication bus 340. The communication bus 340 is used to establish communication between these components. In this embodiment, the communication interface 320 is used for signaling or data communication with other node devices. The memory 330 may be a high-speed RAM or a non-volatile memory, such as at least one disk storage device. Optionally, the memory 330 may also be at least one storage device located remotely from the aforementioned processor. The memory 330 stores computer-readable instructions, which, when executed by the processor 310, cause the electronic device to perform the aforementioned method process.

[0164] Understandable. Figure 3 The structure shown is for illustrative purposes only; the electronic device may also include components that are more advanced than those shown. Figure 3 The more or fewer components shown, or having the same Figure 3 The different configurations shown. Figure 3 The components shown can be implemented using hardware, software, or a combination thereof.

[0165] This application provides a computer-readable storage medium storing a computer program thereon. When the computer program is executed by a processor, it performs the method process executed by the electronic device in the above method embodiments.

[0166] This embodiment discloses a computer program product, which includes a computer program stored on a non-transitory computer-readable storage medium. The computer program includes program instructions, and when the program instructions are executed by a computer, the computer can perform the methods provided in the above-described method embodiments.

[0167] In summary, the embodiments of this application provide a gain control method, electronic device, storage medium, and program product. By simultaneously acquiring received signal strength indications at multiple observation nodes—namely, the analog front-end, the analog-to-digital converter output, and after the baseband filter—and aligning them to a unified reference frame, it effectively solves the problems of incomplete single-point detection information and the inability to directly compare multi-domain power in the prior art. This achieves comprehensive perception of in-band signals, out-of-band interference, and thermal noise. Based on this, the theoretical gain adjustment amount is determined according to the signal strength at the aligned analog-to-digital converter output, and the allocation of analog and digital gain is jointly decided by combining multi-domain information, thereby providing a strong basis for gain allocation decisions and improving the reliability of gain allocation.

[0168] In the embodiments provided in this application, it should be understood that the disclosed apparatus and methods can be implemented in other ways. The apparatus embodiments described above are merely illustrative. For example, the division of units is only a logical functional division, and in actual implementation, there may be other division methods. Furthermore, multiple units or components may be combined or integrated into another system, or some features may be ignored or not executed. Additionally, the displayed or discussed mutual couplings, direct couplings, or communication connections may be through some communication interfaces; indirect couplings or communication connections between devices or units may be electrical, mechanical, or other forms.

[0169] Furthermore, the units described as separate components may or may not be physically separate. The components shown as units may or may not be physical units; that is, they may be located in one place or distributed across multiple network units. Some or all of the units can be selected to achieve the purpose of this embodiment according to actual needs.

[0170] Furthermore, the functional modules in the various embodiments of this application can be integrated together to form an independent part, or each module can exist independently, or two or more modules can be integrated to form an independent part.

[0171] In this document, relational terms such as first and second are used only to distinguish one entity or operation from another entity or operation, without necessarily requiring or implying any such actual relationship or order between these entities or operations.

[0172] The above description is merely an embodiment of this application and is not intended to limit the scope of protection of this application. Various modifications and variations can be made to this application by those skilled in the art. Any modifications, equivalent substitutions, improvements, etc., made within the spirit and principles of this application should be included within the scope of protection of this application.

Claims

1. A gain control method, characterized in that, Applied to a terminal, the method includes: The received signal strength indications of multiple different observation nodes in the receiver are obtained, where the observation nodes are located after the analog front end, the analog-to-digital converter output, and the baseband filter, respectively. Based on the link gain corresponding to each observation node, the received signal strength indication is aligned to a unified reference frame; Based on the received signal strength indication at the output of the aligned analog-to-digital converter, determine the theoretical gain adjustment amount that the receiver needs to achieve; Based on the received signal strength indications after alignment and the theoretical gain adjustment, determine the analog gain and digital gain to be configured; The analog gain and the digital gain are respectively configured to the corresponding devices so that gain control can be performed using the analog gain and the digital gain in the next gain control cycle.

2. The method according to claim 1, characterized in that, The step of determining the analog and digital gain to be configured based on the received signal strength indications after alignment and the theoretical gain adjustment includes: Based on the degree of difference between the received signal strength indication of the analog front end after alignment and the received signal strength indication of the analog-to-digital converter output, a target analog gain allocation table is selected from multiple analog gain allocation tables. The simulation gain is determined based on the target simulation gain allocation table and the theoretical gain adjustment amount; The digital gain is determined based on the difference between the received signal strength indication at the output of the analog-to-digital converter after alignment and the received signal strength indication after the baseband filter, the theoretical gain adjustment, and the analog gain.

3. The method according to claim 2, characterized in that, The step of selecting a target analog gain allocation table from multiple analog gain allocation tables based on the degree of difference between the received signal strength indication at the aligned analog front-end and the received signal strength indication at the analog-to-digital converter output includes: The interference state of the current receiving environment is determined based on the degree of difference between the received signal strength indication of the analog front end after alignment and the received signal strength indication of the analog-to-digital converter output. If the interference state is a strong interference state, then select the target analog gain allocation table with linearity priority from multiple analog gain allocation tables; If the interference state is an interference-free state, then select the target analog gain allocation table with priority given to noise figure from multiple analog gain allocation tables.

4. The method according to claim 2, characterized in that, The step of determining the analog gain based on the target analog gain allocation table and the theoretical gain adjustment includes: Select the target gain from the target analog gain allocation table that has the smallest difference from the theoretical gain adjustment and whose difference from the currently effective total analog gain is within a preset maximum allowable adjustment step size, and determine the target gain as the analog gain.

5. The method according to claim 1, characterized in that, The step of aligning the received signal strength indication to a unified reference frame based on the link gain corresponding to each observation node includes: The signal strength deviation of each observation node is obtained by subtracting the link gain of the corresponding observation node from the received signal strength indication of each observation node. The intensity deviation of each observation node is added to the reference gain of the unified reference system to obtain the received signal strength indication of each observation node after alignment.

6. The method according to claim 1, characterized in that, The step of determining the theoretical gain adjustment amount that the receiver needs to achieve based on the received signal strength indication at the output of the aligned analog-to-digital converter includes: Obtain the deviation between the received signal strength indication at the output of the aligned analog-to-digital converter and the preset target power; The deviation is smoothed by a first-order infinite impulse response low-pass filter to obtain the processed deviation. Based on the processed deviation and the reference gain of the unified reference system, the theoretical gain adjustment amount that the receiver needs to achieve is determined.

7. The method according to claim 1, characterized in that, The unified reference frame can be any one of the following: the antenna port equivalent input power reference frame, the analog-to-digital converter input terminal equivalent power reference frame, and the unified power reference frame under the current analog total gain.

8. The method according to claim 1, characterized in that, The step of configuring the analog gain and the digital gain to the corresponding devices respectively includes: Configure the analog gain to the analog front end; After waiting for a preset time, the digital gain is configured to the digital gain compensation module.

9. An electronic device, characterized in that, It includes a processor and a memory, the memory storing computer-readable instructions that, when executed by the processor, perform the method as described in any one of claims 1-8.

10. A computer-readable storage medium having a computer program stored thereon, characterized in that, When the computer program is executed by a processor, it performs the method as described in any one of claims 1-8.

11. A computer program product, characterized in that, It includes computer program instructions, which, when read and executed by a processor, perform the method as described in any one of claims 1-8.

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