Equivalent discharge amount determination method and device, storage medium and electronic equipment

Abstract

The application discloses an equivalent discharge amount determination method and device, a storage medium and an electronic device. The method comprises the following steps: obtaining a plurality of multi-dimensional signals corresponding to a plurality of channels in a target period; determining a frequency response compensation corresponding to the plurality of channels based on the plurality of multi-dimensional signals corresponding to the plurality of channels, wherein the frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to a reference channel, and the reference channel is determined based on the signal-to-noise ratio of the plurality of channels; performing consistency calibration on partial discharge pulse signals in the plurality of multi-dimensional signals corresponding to the plurality of channels based on the frequency response compensation corresponding to the plurality of channels to obtain target calibration signals corresponding to the plurality of channels; and determining equivalent discharge amounts corresponding to the plurality of channels based on the target calibration signals corresponding to the plurality of channels. The application solves the technical problem that the determination result of the equivalent discharge amount of the channel connected with the live indicator is inaccurate in the related art.

Description

Technical Field

[0001] This application relates to the field of power systems, and more specifically, to a method, apparatus, storage medium, and electronic device for determining equivalent discharge quantity. Background Technology

[0002] With the continuous improvement of the intelligence level of power distribution networks, live-line testing has become an important means of assessing the insulation status of high-voltage switchgear. Live-line indicators are standard components of 10kV high-voltage switchgear, installed at the wall bushing in the busbar compartment. They achieve the function of indicating the live state by capacitively coupling and sensing the power frequency electric field of the high-voltage conductor inside the switchgear.

[0003] In recent years, utilizing the capacitive coupling channel of a live indicator to pick up partial discharge (PD) pulse signals (250kHz to 100MHz frequency band) has gradually become a novel pulse coupling detection technology. The core advantage of this technology is that it eliminates the need for additional sensors, directly reusing existing live indicators in the switchgear as pulse coupling sensing nodes. It enables multi-point synchronous detection without power interruption or disassembly, offering advantages such as undisturbed installation, low cost, and standardized deployment. In a multi-point pulse coupling detection system, if each of the A, B, and C phases of different switchgear is equipped with a live indicator, a three-channel distributed sensing array can be naturally formed, supporting multi-channel collaborative quantitative analysis of equivalent discharge quantities. However, existing technologies suffer from the following significant drawbacks, severely limiting the quantitative analysis accuracy of live indicator pulse coupling detection technology and leading to inaccurate determination of the equivalent discharge quantities of the channels connected to the live indicators:

[0004] (1) The coupling characteristics of the live indicators of each channel are very different, which makes it impossible to directly compare the amplitudes of multiple channels;

[0005] (2) Existing technology relies on an external standard signal source for calibration, which has poor engineering practicality;

[0006] (3) The differences in frequency response characteristics of each channel were not included in the calibration system, and the wideband amplitude distortion was not corrected;

[0007] (4) The coupling characteristic drift caused by aging cannot be detected in real time.

[0008] There is currently no effective solution to the above problems. Summary of the Invention

[0009] This application provides a method, apparatus, storage medium, and electronic device for determining equivalent discharge quantity, so as to at least solve the technical problem in the related art that the determination result of the equivalent discharge quantity of the channel connected to the charged indicator is inaccurate.

[0010] According to one aspect of the embodiments of this application, a method for determining equivalent discharge quantity is provided, comprising: acquiring multi-dimensional signals corresponding to multiple channels within a target period, wherein the multi-dimensional signals include a power frequency coupling signal output by a charged indicator connected to the corresponding channel, a background noise signal, and a partial discharge pulse signal; determining frequency response compensation corresponding to multiple channels based on the multi-dimensional signals corresponding to the multiple channels, wherein the frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to a reference channel, and the reference channel is determined based on the signal-to-noise ratio corresponding to the multiple channels; performing consistency calibration on the partial discharge pulse signals in the multi-dimensional signals corresponding to the multiple channels based on the frequency response compensation corresponding to the multiple channels to obtain target calibration signals corresponding to the multiple channels; and determining the equivalent discharge quantity corresponding to the multiple channels based on the target calibration signals corresponding to the multiple channels.

[0011] According to another aspect of the embodiments of this application, an equivalent discharge quantity determination device is provided, comprising: a data acquisition module, configured to acquire multi-dimensional signals corresponding to multiple channels within a target period, wherein the multi-dimensional signals include a power frequency coupling signal output by a charged indicator connected to the corresponding channel, a background noise signal, and a partial discharge pulse signal; a first determination module, configured to determine frequency response compensation corresponding to multiple channels based on the multi-dimensional signals corresponding to the multiple channels, wherein the frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to a reference channel, and the reference channel is determined based on the signal-to-noise ratio corresponding to the multiple channels; a consistency calibration module, configured to perform consistency calibration on the partial discharge pulse signals in the multi-dimensional signals corresponding to the multiple channels based on the frequency response compensation corresponding to the multiple channels, to obtain target calibration signals corresponding to the multiple channels; and a second determination module, configured to determine the equivalent discharge quantity corresponding to the multiple channels based on the target calibration signals corresponding to the multiple channels.

[0012] According to another aspect of the embodiments of this application, a non-volatile storage medium is provided, which stores a plurality of instructions, any one of which is adapted to be loaded by a processor to determine the equivalent discharge quantity.

[0013] According to another aspect of the embodiments of this application, an electronic device is provided, including: one or more processors and a memory, the memory being used to store one or more programs, wherein when the one or more programs are executed by the one or more processors, the one or more processors implement any one of the equivalent discharge quantity determination methods.

[0014] According to another aspect of the embodiments of this application, a computer program product is provided, which, when executed on a data processing device, is adapted to perform the steps of the method for determining the equivalent discharge quantity.

[0015] In this embodiment, multi-dimensional signals corresponding to multiple channels within a target period are acquired. These multi-dimensional signals include the power frequency coupling signal output by the live indicator connected to the corresponding channel, background noise signal, and partial discharge pulse signal. Based on these multi-dimensional signals, frequency response compensations for each channel are determined. The frequency response compensations describe the frequency response difference between the corresponding channel and a reference channel, which is determined based on the signal-to-noise ratio of each channel. Based on these frequency response compensations, the partial discharge pulse signals in the multi-dimensional signals corresponding to each channel are uniformly calibrated to obtain target calibration signals for each channel. Based on these target calibration signals, the equivalent discharge quantity for each channel is determined. This achieves the goal of determining the frequency response compensation for each channel based on the multi-dimensional signals, thereby uniformly calibrating the partial discharge pulse signals of each channel. This improves the accuracy of determining the equivalent discharge quantity of the channel connected to the live indicator by uniformly calibrating the partial discharge pulse signals of each channel, thus solving the technical problem of inaccurate determination of the equivalent discharge quantity of the channel connected to the live indicator in related technologies. Attached Figure Description

[0016] The accompanying drawings, which are included to provide a further understanding of this application and form part of this application, illustrate exemplary embodiments and are used to explain this application, but do not constitute an undue limitation of this application. In the drawings:

[0017] Figure 1 This is a flowchart of a method for determining equivalent discharge quantity according to an embodiment of this application;

[0018] Figure 2 This is a flowchart of an optional method for determining the equivalent discharge quantity according to an embodiment of this application;

[0019] Figure 3 This is a schematic diagram of an equivalent discharge quantity determination device according to an embodiment of this application;

[0020] Figure 4 This is a structural diagram of an electronic device provided according to an embodiment of this application. Detailed Implementation

[0021] To enable those skilled in the art to better understand the present application, the technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of the present application, and not all embodiments. Based on the embodiments in the present application, all other embodiments obtained by those of ordinary skill in the art without creative effort should fall within the scope of protection of the present application.

[0022] It should be noted that the terms "first," "second," etc., in the specification, claims, and accompanying drawings of this application are used to distinguish similar objects and are not necessarily used to describe a specific order or sequence. It should be understood that such data can be interchanged where appropriate so that the embodiments of this application described herein can be implemented in orders other than those illustrated or described herein. Furthermore, the terms "comprising" and "having," and any variations thereof, are intended to cover non-exclusive inclusion; for example, a process, method, system, product, or apparatus that comprises a series of steps or units is not necessarily limited to those steps or units explicitly listed, but may include other steps or units not explicitly listed or inherent to such processes, methods, products, or apparatus.

[0023] It should be noted that the information collected in this application (including but not limited to multi-dimensional signals corresponding to multiple channels, signal-to-noise ratios corresponding to multiple channels, etc.) and data are information and data authorized by the user or fully authorized by all parties. Furthermore, the collection, storage, use, processing, transmission, provision, disclosure, and application of related data all comply with relevant laws, regulations, and standards, necessary confidentiality measures have been taken, and they do not violate public order and good morals. Corresponding operation entry points are provided for users to choose to authorize or refuse. For example, interfaces are set up between this system and relevant users or institutions, providing users with corresponding operation entry points for them to choose to agree to or refuse automated decision results; if the user chooses to refuse, the process proceeds to the expert decision-making stage.

[0024] According to an embodiment of this application, a method embodiment for determining equivalent discharge quantity is provided. It should be noted that the steps shown in the flowchart in the accompanying drawings can be executed in a computer system such as a set of computer-executable instructions. Furthermore, although a logical order is shown in the flowchart, in some cases, the steps shown or described may be executed in a different order than that shown here.

[0025] Figure 1 This is a flowchart of a method for determining equivalent discharge quantity according to an embodiment of this application, such as... Figure 1 As shown, the method includes the following steps:

[0026] Step S102: Obtain the multi-dimensional signals corresponding to multiple channels within the target period, wherein the multi-dimensional signals include the power frequency coupling signal output by the live indicator connected to the corresponding channel, the background noise signal, and the partial discharge pulse signal;

[0027] It is understandable that by synchronously acquiring power frequency coupling signals, background noise signals, and partial discharge pulse signals, complete and multi-dimensional basic data support can be provided for subsequent identification of equivalent circuit parameters and multi-channel frequency domain consistency calibration.

[0028] Optionally, the power frequency coupling output signals of each energized indicator can be synchronously acquired by the acquisition circuits of each channel during the PD detection interval, and the power frequency voltage amplitude can be extracted. and phase This serves as an excitation reference for subsequent channel identification (used to determine the initial equivalent coupling capacitance, series inductance, and loss resistance of the equivalent circuit of the charged indicator).

[0029] Optionally, within each power frequency cycle (20 milliseconds), the PD detection window and the power frequency sampling window are set to alternate: PD detection window duration (e.g., 10 milliseconds), sampling rate not less than 250 MSPS (millions of samples per second), used to acquire partial discharge pulse signals and background noise signals of each channel; power frequency sampling window duration (For example, 10 milliseconds), the power frequency coupled signals of each channel are acquired at a low sampling rate (≥10kSPS). The two sampling windows are switched by an analog switch to avoid interference, and the total detection duty cycle is not less than 50%.

[0030] Step S104: Based on the multi-dimensional signals corresponding to multiple channels, determine the frequency response compensation corresponding to each of the multiple channels. The frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to the reference channel. The reference channel is determined based on the signal-to-noise ratio corresponding to each of the multiple channels.

[0031] It is understandable that the above frequency response compensation can be represented by a function, namely the frequency response compensation function. By selecting the reference channel based on the signal-to-noise ratio and constructing the frequency response compensation, amplitude distortion and waveform distortion caused by differences in sensor models and hardware inconsistencies among multiple channels can be adaptively eliminated, laying the foundation for subsequent high-precision multi-channel signal consistency calibration.

[0032] In one optional embodiment, determining the frequency response compensation for each of the multiple channels based on the multidimensional signals corresponding to each of the multiple channels includes: determining a parameter set for each of the multiple channels based on the multidimensional signals corresponding to each of the multiple channels, wherein the parameter set includes the target equivalent coupling capacitance, series inductance, and loss resistance of the equivalent circuit of the charged indicator connected to the corresponding channel; determining the frequency response for each of the multiple channels based on the parameter set for each of the multiple channels, wherein the frequency response is used to characterize the amplitude-frequency and phase-frequency characteristics of the corresponding channel to the partial discharge pulse signal; determining the channel with the highest signal-to-noise ratio among the multiple channels as the reference channel; and determining the frequency response compensation for each of the multiple channels as the ratio between the frequency response of the reference channel and the frequency responses of the multiple channels respectively.

[0033] It is understandable that, based on the multidimensional signals corresponding to multiple channels collected, and based on the equivalent circuit model of the charged indicator connected to the channels, the parameter sets corresponding to each channel are determined. These parameters include the target equivalent coupling capacitance, series inductance, and loss resistance of the equivalent circuit of the charged indicator connected to the corresponding channel (which can be modeled as an LCR series network). Based on the parameter sets corresponding to each channel, the frequency response corresponding to each channel is determined. This frequency response can be represented by a function, i.e., a frequency response function. The channel with the highest signal-to-noise ratio among the multiple channels is determined as the reference channel. The frequency response compensation for each channel is determined by the ratio between the frequency response of the reference channel and the frequency responses of the multiple channels. By constructing frequency response compensation using the channel with the highest signal-to-noise ratio as the reference channel, amplitude distortion and phase distortion caused by differences in charged indicator models, aging drift, and hardware inconsistencies among the multiple channels can be adaptively eliminated. This achieves high consistency normalization of the multi-channel partial discharge pulse signals over a wide bandwidth, providing a reliable signal basis for subsequent quantitative analysis of the equivalent discharge quantity.

[0034] Optionally, the channel with the highest signal-to-noise ratio is selected as the reference channel because it receives the partial discharge pulse signal with the highest fidelity and is least affected by noise interference. Using it as a reference can minimize the transmission of noise errors during the calibration process and ensure the accuracy and reliability of multi-channel consistency calibration.

[0035] In one optional embodiment, the parameter sets corresponding to the multiple channels are determined based on the multi-dimensional signals corresponding to the multiple channels, including: determining the fundamental amplitude of the multiple channels based on the power frequency coupling signal in the multi-dimensional signals corresponding to the multiple channels; determining the resonant frequency of the multiple channels based on the background noise signal in the multi-dimensional signals corresponding to the multiple channels, wherein the resonant frequency is used to characterize the frequency point at which the amplitude-frequency response of the equivalent circuit of the live indicator connected to the corresponding channel reaches a peak within a preset frequency band; and determining the parameter sets corresponding to the multiple channels based on the fundamental amplitude and the resonant frequency of the multiple channels.

[0036] It is understandable that, based on the power frequency coupled signals in the multidimensional signals corresponding to multiple channels, the Discrete Fourier Transform (DFT) is used to determine the fundamental amplitude values ​​corresponding to each channel. The Welch method (a statistical estimation technique based on segmentation, windowing, and averaging to reduce power spectrum estimation variance and improve spectral resolution) is used to calculate the power spectral density (PSD) estimate for the background noise signal of each channel. Within a preset frequency band (e.g., 250kHz to 100MHz), the peak point of the power spectral density curve is found, and the frequency corresponding to this peak is determined as the resonant frequency of that channel. This frequency characterizes the location where the LCR series network inside the charged indicator (i.e., the equivalent circuit of the charged indicator) resonates and the amplitude-frequency response reaches its maximum. Based on the fundamental amplitude values ​​and resonant frequencies corresponding to multiple channels, the parameter sets corresponding to each channel are determined. By extracting the fundamental amplitude using power frequency coupling signals and combining it with the resonant frequencies corresponding to multiple channels to calculate the parameter sets corresponding to multiple channels, accurate and adaptive identification of the parameter sets of the equivalent circuit of a multi-channel live indicator is achieved without relying on an external standard source. This provides a key parameter basis for eliminating amplitude and phase distortion between channels and achieving high-precision consistency calibration.

[0037] Optionally, the sampling sequence of the m-th channel within the power frequency sampling window of each channel. (i.e., the power frequency coupled signal at acquisition time t), and the voltage amplitude (i.e., the fundamental frequency amplitude) of the 50Hz (Hertz, i.e., power frequency) fundamental component is extracted by Discrete Fourier Transform (DFT). and phase :

[0038]

[0039] in, Let V be the fundamental voltage amplitude (V) of the power frequency coupled signal of the m-th channel. Let be the fundamental phase of the power frequency coupled signal of the m-th channel. The sampling interval is... This is the time-domain sampled signal (i.e., the power frequency coupled signal) of the m-th channel. The imaginary unit, For frequency domain indexing, This represents the total number of sampling points.

[0040] Optionally, the rationality of the extracted channel phase can be verified using the theoretical relationship of the three-phase power frequency voltage phase (i.e., phases A, B, and C are successively 120° out of phase). If the deviation of the phase difference between channels from 120° exceeds a threshold... If the error is 10°, the channel is determined to be abnormal (e.g., there is interference or sampling failure), triggering the abnormal channel marker. The power frequency coupling signal of that channel will not participate in the current identification.

[0041] Optionally, the above power spectral density estimate is a specific numerical result or mathematical function obtained by calculation, while the power spectral density curve is a visual graphical representation of the numerical result in the frequency domain (i.e., the horizontal axis is frequency, the vertical axis is power spectral density amplitude, and the vertical axis value of each point on the curve is the power spectral density estimate at that frequency point).

[0042] In one optional embodiment, based on the fundamental amplitude and resonant frequency corresponding to each of the multiple channels, a parameter set corresponding to each of the multiple channels is determined, including: determining the initial equivalent coupling capacitance corresponding to each of the multiple channels based on the fundamental amplitude; determining the series inductance corresponding to each of the multiple channels based on the initial equivalent coupling capacitance and resonant frequency corresponding to each of the multiple channels; determining the loss resistance corresponding to each of the multiple channels based on the initial equivalent coupling capacitance and series inductance corresponding to each of the multiple channels; correcting the initial equivalent coupling capacitance corresponding to each of the multiple channels to obtain the target equivalent coupling capacitance corresponding to each of the multiple channels; and determining the parameter set corresponding to each of the multiple channels based on the series inductance, loss resistance, and target equivalent coupling capacitance corresponding to each of the multiple channels.

[0043] It can be understood that, based on the fundamental amplitude values ​​corresponding to multiple channels, the initial equivalent coupling capacitance (i.e., the equivalent coupling capacitance without correction based on the historical equivalent coupling capacitance of the previous cycle) for each channel is determined. Based on the initial equivalent coupling capacitance and the resonant frequency of each channel, the series inductance for each channel is determined. Based on the initial equivalent coupling capacitance, the series inductance, and the quality factor of each channel, the loss resistance for each channel is determined. Based on the historical equivalent coupling capacitance of each channel in the previous cycle, the initial equivalent coupling capacitance is corrected to obtain the target equivalent coupling capacitance for each channel. The series inductance, loss resistance, and target equivalent coupling capacitance for each channel are then defined as the parameter set for each channel. Through this process, the accurate and stable acquisition of the equivalent circuit parameter set of the charged indicator is achieved, providing a highly reliable parameter basis for eliminating coupling differences and frequency response distortion between channels and ensuring the accuracy of quantitative detection of multi-channel equivalent discharge.

[0044] Optionally, the parameter identification equations of the high-frequency equivalent circuit (i.e., equivalent circuit) of the charged indicator can be established using the power frequency excitation-response pair as input, and the initial equivalent coupling capacitance of each channel can be solved by nonlinear least squares fitting. Series inductor Loss resistance Key parameters, etc.

[0045] Optionally, the high-frequency equivalent circuit of the live indicator connected to the m-th channel is modeled as a series LCR network: the equivalent coupling capacitance (i.e., the initial equivalent coupling capacitance) is capacitively coupled to the high-voltage conductor; the equivalent series inductance (i.e., the series inductance) is generated by the leads and internal windings; the equivalent loss resistance (i.e., the loss resistance) includes the dielectric loss and the lead resistance. The equivalent impedance of this network is... for:

[0046]

[0047] in, Let f be the equivalent impedance of the m-th channel at frequency f. The equivalent loss resistance (i.e., loss resistance) of the high-frequency equivalent circuit of the live indicator connected to the m-th channel. The equivalent series inductance (i.e., series inductance) of the high-frequency equivalent circuit of the live indicator connected to the m-th channel. Let f be the equivalent coupling capacitance (i.e., the initial equivalent coupling capacitance) of the high-frequency equivalent circuit of the charged indicator connected to the m-th channel, and f be the frequency of the signal.

[0048] Optionally, at power frequency Under Hz conditions, the open-circuit output voltage amplitude (i.e., fundamental frequency amplitude) at the leads of the live indicator. With the power frequency voltage amplitude of high voltage conductors The relationship between them is determined by capacitive voltage division. The input impedance of the acquisition circuit... Connecting it in series with the equivalent circuit, the power frequency response equation is established:

[0049]

[0050] in, This is the equivalent impedance of a live indicator at power frequency. This is the lead wire transmission loss factor.

[0051] Alternatively, since the inductive and capacitive reactances at power frequency are much greater than the input impedance of the acquisition circuit, The power frequency response equation can be simplified to a purely capacitive voltage divider model, thus allowing for direct solution. :

[0052]

[0053] Optionally, the high-frequency background noise signal acquired within the PD detection window (i.e., the background noise signal, acquired during the non-PD discharge period within the detection window) is used as a broadband excitation, and the resonant frequency of the equivalent circuit is identified by power spectral density estimation. And thus, it can be deduced The resonant frequency of the high-frequency equivalent circuit of the charged indicator connected to the m-th channel. for:

[0054]

[0055] in, The peak value is determined by estimating the power spectral density of the background noise signal.

[0056] Optionally, after determining Afterwards, combined Determine the channel's loss resistance based on the channel's quality factor. .

[0057] Optionally, during the silent period without PD discharge (determined by threshold detection), the power spectral density estimate of the background noise signal of the m-th channel is calculated using the Welch method. :

[0058]

[0059] in, It is the Welch power spectral density estimate of the background noise signal in the m-th channel; The total number of Welch segments; For Hamming window functions; is the k-th segment of the background noise signal in the m-th channel; N is the number of signal points in each segment of the background noise signal.

[0060] Optionally, the quality factor is used to characterize the sharpness of the resonant peak at the resonant frequency of the power spectral density curve. It can be determined as follows: Based on the power spectral density curve, determine the peak power value corresponding to the resonant frequency, and the two cutoff frequencies corresponding to the peak power value dropping to half. Calculate the difference between these two cutoff frequencies as the bandwidth, and determine the ratio of the resonant frequency to the bandwidth as the quality factor.

[0061] Optionally, based on the obtained parameter set { , , } Calculate the equivalent impedance corresponding to the m-th channel. Then, the frequency response function between the open-circuit output voltage of the m-th channel at frequency f and the input PD excitation current is obtained. for:

[0062]

[0063] in, Let f be the frequency response function of the m-th channel, describing the amplitude-frequency and phase-frequency characteristics of the PD excitation signal after coupling through the charged indicator at the acquisition end; Let f be the input impedance of the m-th channel acquisition circuit at frequency f; The amplitude response of m channels at frequency f reflects the coupling gain of the channel to the PD pulse signal at that frequency; This is the estimated target equivalent coupling capacitance value for the m-th channel after EWMA update for the d-th power frequency cycle.

[0064] Optionally, the channel with the highest signal-to-noise ratio is selected as the reference channel (numbered ref), and its frequency response function is denoted as... The frequency response compensation function of the remaining channels relative to the reference channel. Defined as:

[0065]

[0066] in, Let be the frequency response compensation function of the m-th channel relative to the reference channel, which is the core conversion coefficient for calibrating the PD pulse signal of each channel. When m = 1 (i.e., m is the reference channel), no compensation is needed; when | When |>1, it indicates that the coupling gain of the m-th channel to this frequency component is lower than that of the reference channel, requiring amplification compensation; when | Attenuation compensation is required when |<1; It also includes phase compensation to correct phase response differences between channels and ensure the alignment accuracy of the partial discharge pulse signal waveform.

[0067] In one optional embodiment, the initial equivalent coupling capacitances corresponding to multiple channels are corrected to obtain the target equivalent coupling capacitances corresponding to multiple channels, including: obtaining the historical equivalent coupling capacitances corresponding to multiple channels in the previous period before the target period; and correcting the initial equivalent coupling capacitances corresponding to multiple channels based on the historical equivalent coupling capacitances corresponding to multiple channels to obtain the target equivalent coupling capacitances corresponding to multiple channels.

[0068] It can be understood that the historical equivalent coupling capacitances of multiple channels in the previous cycle before the target cycle are obtained. Based on the historical equivalent coupling capacitances of multiple channels, an exponentially weighted moving average (EWMA) method is used to correct the initial equivalent coupling capacitances of multiple channels, thus obtaining the target equivalent coupling capacitances of multiple channels. By introducing the exponentially weighted moving average mechanism, the current initial equivalent coupling capacitance is smoothly corrected using historical equivalent coupling capacitances. This effectively suppresses random noise interference and enables adaptive tracking of the long-term aging drift of the coupling characteristics of the charged indicator, improving the accuracy of the target equivalent coupling capacitance determination results, and thus improving the quantitative detection accuracy of the equivalent discharge quantity.

[0069] Optionally, it is updated once per power frequency cycle. The identification value (i.e., the initial equivalent coupling capacitance) is updated using an exponentially weighted moving average (EWMA) method to achieve online tracking of the aging drift of the charged indicator, thus obtaining the target equivalent coupling capacitance of the high-frequency equivalent circuit of the charged indicator connected to the m-th channel:

[0070]

[0071] in, This is the estimated target equivalent coupling capacitance value for the m-th channel after EWMA update for the d-th power frequency cycle; The target equivalent coupling capacitance (i.e., the historical equivalent coupling capacitance of the m-th channel in the previous cycle before the d-th power frequency cycle) is estimated after EWMA update for d-1 power frequency cycles. For the d-th power frequency cycle, the initial equivalent coupling capacitance corresponding to the m-th channel is obtained based on the power frequency response; It is a forgetting factor.

[0072] Step S106: Based on the frequency response compensation corresponding to each of the multiple channels, perform consistency calibration on the partial discharge pulse signals in the multidimensional signals corresponding to each of the multiple channels to obtain the target calibration signals corresponding to each of the multiple channels.

[0073] It is understandable that by performing consistency calibration on multi-channel partial discharge pulse signals, amplitude distortion and phase shift caused by differences in coupling characteristics and frequency response between channels can be eliminated, achieving high consistency normalization of pulse waveforms in each channel, thereby providing a unified benchmark for subsequent accurate quantitative calculation of channel equivalent discharge quantities.

[0074] In one optional embodiment, based on the frequency response compensation corresponding to each of the multiple channels, the partial discharge pulse signals in the multidimensional signals corresponding to the multiple channels are subjected to consistency calibration to obtain target calibration signals corresponding to the multiple channels, including: performing frequency domain transformation on the partial discharge pulse signals in the multidimensional signals corresponding to the multiple channels to obtain frequency domain signals corresponding to the multiple channels; obtaining frequency domain calibration signals corresponding to the multiple channels based on the frequency response compensation corresponding to the multiple channels and the frequency domain signals corresponding to the multiple channels; and performing inverse transformation on the frequency domain calibration signals corresponding to the multiple channels to obtain target calibration signals corresponding to the multiple channels.

[0075] It is understandable that a Fast Fourier Transform (FFT) is used to perform frequency domain transformation on the partial discharge pulse signals in the multidimensional signals corresponding to multiple channels, resulting in frequency domain signals for each channel. Frequency response compensation is then applied to these channels to achieve consistent calibration of the partial discharge pulse signals across multiple channels, yielding frequency domain calibration signals for each channel. An Inverse Fast Fourier Transform (IFFT) is then used to perform an inverse transformation on these frequency domain calibration signals, resulting in target calibration signals for each channel, which are time-domain signals. By applying frequency response compensation based on an equivalent circuit parameter set for consistent calibration in the frequency domain, amplitude distortion and phase deviation caused by differences in coupling coefficients and high-frequency resonance characteristics between channels are eliminated. This provides a high-quality signal foundation with waveform alignment and comparable amplitude for quantitative analysis of the equivalent discharge quantity across multiple channels.

[0076] Optionally, the raw PD pulse signal acquired by the m-th channel within the PD detection window... Perform a Fast Fourier Transform (FFT) to obtain the frequency domain signal. :

[0077]

[0078] in, Let N be the spectrum (i.e., frequency domain signal) of the PD pulse signal of the m-th channel, where N is the number of FFT points and n is the sampling point number, n = 0, 1, 2, ..., N-1.

[0079] Optionally, With the corresponding frequency response compensation function The signals are multiplied to complete frequency response compensation, and then subjected to inverse Fourier transform (IFFT) to recover the calibrated time-domain calibration signal (i.e., the target calibration signal). :

[0080]

[0081] in, Let m be the time-domain calibration signal of the m-th channel after frequency response compensation, and let each channel be normalized to the reference channel response; The frequency domain calibration signal corresponding to the m-th channel.

[0082] Step S108: Based on the target calibration signals corresponding to the multiple channels respectively, determine the equivalent discharge quantity corresponding to the multiple channels respectively.

[0083] It is understandable that by calculating the equivalent discharge quantity of a channel based on the target calibration signal after consistency calibration, the influence of the difference in coupling coefficient between channels and frequency response distortion on the measurement results can be eliminated, thereby achieving high-precision quantitative measurement of the equivalent discharge quantity of each channel.

[0084] In one optional embodiment, determining the equivalent discharge quantity corresponding to each of the multiple channels based on the target calibration signals corresponding to each of the multiple channels includes: determining the ratio between the target equivalent coupling capacitance of the reference channel and the target equivalent coupling capacitance corresponding to each of the multiple channels as the normalization coefficient corresponding to each of the multiple channels; obtaining the normalized calibration signal corresponding to each of the multiple channels based on the normalization coefficient corresponding to each of the multiple channels and the target calibration signal corresponding to each of the multiple channels; and determining the equivalent discharge quantity corresponding to each of the multiple channels based on the normalized calibration signal corresponding to each of the multiple channels and the target equivalent coupling capacitance of the reference channel.

[0085] It can be understood that the ratio between the target equivalent coupling capacitance of the reference channel and the target equivalent coupling capacitance of each of the multiple channels is determined as the normalization coefficient for each of the multiple channels. The normalization coefficients for each of the multiple channels are then multiplied by their respective target calibration signals to obtain the normalized calibration signals for each of the multiple channels. Based on the normalized calibration signals for each of the multiple channels and the target equivalent coupling capacitance of the reference channel, the equivalent discharge quantity for each of the multiple channels is calculated. By introducing a normalization coefficient based on the target equivalent coupling capacitance to correct the amplitude of the target calibration signal, the signal amplitude deviation caused by the difference in coupling capacitance of the charged indicator between different channels is eliminated. This achieves consistent normalization of the amplitude of the multi-channel partial discharge pulse signal, improving the accuracy and comparability of the equivalent discharge quantity determination results for each channel.

[0086] Optionally, based on the target equivalent coupling capacitance identified for each channel and updated via EWMA. Calculate the static amplitude normalization coefficient of each channel relative to the reference channel. :

[0087]

[0088] in, This is the amplitude normalization coefficient corresponding to the m-th channel; The target equivalent coupling capacitance of the reference channel.

[0089] Optionally, the equivalent discharge quantity of each channel is calculated based on the normalized calibration signal of each channel. :

[0090]

[0091]

[0092] in, Let be the equivalent discharge quantity of the m-th channel. Let be the input capacitor of the m-th channel acquisition circuit. Let m be the normalized calibration signal for the m-th channel. The duration of a single PD pulse signal.

[0093] Through the above steps S102 to S108, the frequency response compensation corresponding to multiple channels can be determined based on the multi-dimensional signals corresponding to multiple channels, thereby achieving the purpose of consistent calibration of the partial discharge pulse signals of each channel. This achieves the technical effect of improving the accuracy of the determination result of the equivalent discharge quantity of the channel connected to the charged indicator by consistent calibration of the partial discharge pulse signals of each channel, and thus solves the technical problem of inaccurate determination result of the equivalent discharge quantity of the channel connected to the charged indicator in related technologies.

[0094] The related technologies for partial discharge pulse signal consistency calibration and channel equivalent discharge quantity determination based on charged indicators have the following shortcomings:

[0095] (1) The coupling characteristics of the live indicators of each channel are very different, which makes it impossible to directly compare the amplitudes of multiple channels;

[0096] In the high-voltage switchgear currently in operation, the live indicators come from dozens of different manufacturers and vary in model. The equivalent coupling capacitance between these indicators and the high-voltage conductors differs greatly (typically ranging from 1 pF to 50 pF), with deviations reaching up to 50 times. The PD pulse signal (i.e., partial discharge pulse signal) generated by the same discharge source exhibits order-of-magnitude differences in signal amplitude at the output terminals of different live indicators. In existing technical solutions, the amplitude of the PD pulse signal acquired from each channel is directly used for comparison and location, without considering the differences in coupling coefficients between channels. This leads to: the amplitude comparison results of the location algorithm losing physical meaning; the inability to quantitatively calculate the equivalent discharge quantity due to the lack of channel coupling coefficients; and the failure of lateral comparisons between detection results from multiple switchgear units.

[0097] (2) Existing technology relies on an external standard signal source for calibration, which has poor engineering practicality;

[0098] Existing channel consistency calibration methods for multi-channel PD testing devices require pausing data acquisition during testing, injecting a standard partial discharge pulse signal with known amplitude and frequency into the switchgear under test, and calculating the relative calibration coefficient by the ratio of the response amplitudes of each channel. This method has the following drawbacks: it requires an additional standard pulse generator, increasing equipment costs; selecting the injection point for the standard partial discharge pulse signal is difficult, as different injection points lead to different propagation paths, resulting in insufficient representativeness of the calibration coefficient; the calibration process requires interruption of normal testing, making online continuous calibration impossible; and different models of live indicators have different frequency response characteristics, meaning a single-frequency standard pulse cannot reflect the differences in coupling characteristics across a wide frequency band.

[0099] (3) The differences in frequency response characteristics of each channel were not included in the calibration system, and the wideband amplitude distortion was not corrected;

[0100] The high-frequency equivalent circuit of a live indicator is not a pure capacitor, but a complex LCR network composed of coupling capacitors, distributed inductance, dielectric loss resistance, and lead resistance. This network exhibits significant resonance and attenuation characteristics in the 250kHz–100MHz frequency band, and the resonant frequencies vary among different live indicator models (typically ranging from 5MHz to 80MHz). Existing technologies ignore these frequency response differences, only correcting each channel with a single amplitude coefficient. This leads to frequency-dependent distortion of the partial discharge pulse signal waveform across a wide frequency band, affecting the accuracy of subsequent PRPD (Phase-Resolved Partial Discharge) spectrum analysis and discharge type identification.

[0101] (4) The coupling characteristic drift caused by aging cannot be detected in real time.

[0102] Live indicators operate under varying electric fields, temperatures, and humidity conditions over extended periods. The aging of their internal insulation causes drift in coupling capacitance and loss tangent, leading to long-term changes in the coupling characteristics of the detection channel. Current technologies employ a one-time factory calibration, which fails to track characteristic drift during operation, resulting in a continuous decline in quantitative detection accuracy as the device ages.

[0103] To address the four deficiencies mentioned above, the core technical problem to be solved is: without using any external standard signal source and without interrupting normal detection, to fully utilize the power frequency coupling signal generated by the live indicator itself under normal working conditions, to automatically identify the wideband coupling characteristics of each channel live indicator (based on the quantitative characterization of the parameter set of the determined equivalent circuit), and thereby achieve real-time consistency calibration of multi-channel partial discharge pulse signals and accurate determination of the equivalent discharge quantity of the channel.

[0104] Based on the above embodiments and optional embodiments, this application proposes an optional implementation method for determining the equivalent discharge quantity. This optional implementation method provides a multi-channel partial discharge pulse signal consistency calibration method and a channel equivalent discharge quantity determination method based on the self-identification of the coupling characteristics of charged indicators. Under the condition of not requiring external standard partial discharge pulse signal injection and without interrupting online detection, the power frequency coupling voltage signal (i.e., power frequency coupling signal) output by each channel charged indicator itself is used as a built-in calibration reference source. Through wideband system identification under power frequency excitation, the equivalent circuit parameter set of each channel charged indicator is automatically extracted, and the frequency response compensation function of each channel (i.e., frequency response compensation represented by a function) is constructed. Real-time consistency calibration is performed on the PD pulse signals (i.e., partial discharge pulse signals) collected from multiple channels, eliminating the difference in coupling coefficients between channels and frequency response distortion, and achieving the engineering accuracy target of quantitative error of equivalent discharge quantity of each channel not exceeding ±10%.

[0105] Figure 2 This is a flowchart of an optional method for determining the equivalent discharge quantity according to an embodiment of this application, such as... Figure 2 As shown, the steps of a multi-channel partial discharge pulse signal consistency calibration method and a channel equivalent discharge quantity determination method based on the self-identification of the coupling characteristics of charged indicators include:

[0106] Step S1: Synchronous acquisition of multi-channel power frequency coupled signals and extraction of power frequency parameters.

[0107] The power frequency coupling output signals of each live indicator are synchronously acquired by the acquisition circuits of each channel during the PD detection interval, and the power frequency voltage amplitude is extracted. and phase This serves as an excitation reference for subsequent channel identification (used to determine the initial equivalent coupling capacitance, series inductance, and loss resistance of the equivalent circuit of the charged indicator).

[0108] Step S11: Set the sampling window for the power frequency coupled signal.

[0109] Within each power frequency cycle (20 milliseconds), the PD detection window and the power frequency sampling window are set to alternate: PD detection window duration (Default 10 milliseconds), sampling rate not less than 250 MSPS (millions of samples per second), used to acquire partial discharge pulse signals and background noise signals of each channel; power frequency sampling window duration (Default 10 milliseconds) The power frequency coupled signal of each channel is acquired at a low sampling rate (≥10kSPS). The two sampling windows are switched by an analog switch to avoid interference, and the total detection duty cycle is not less than 50%.

[0110] Step S12: Extraction of power frequency fundamental wave parameters.

[0111] The sampling sequence of the m-th channel within the power frequency sampling window of each channel (i.e., the power frequency coupled signal at acquisition time t), and the voltage amplitude (i.e., the fundamental frequency amplitude) of the 50Hz (Hertz, i.e., power frequency) fundamental component is extracted by Discrete Fourier Transform (DFT). and phase :

[0112]

[0113] in, Let V be the fundamental voltage amplitude (V) of the power frequency coupled signal of the m-th channel. Let be the fundamental phase of the power frequency coupled signal of the m-th channel. The sampling interval is... This is the time-domain sampled signal (i.e., the power frequency coupled signal) of the m-th channel. The imaginary unit, For frequency domain indexing, This represents the total number of sampling points.

[0114] Step S13: Verification of the three-phase relationship.

[0115] The rationality of the extracted channel phases is verified using the theoretical relationship of three-phase power frequency voltage (i.e., phases A, B, and C are 120° out of phase sequentially). If the phase difference between channels deviates from 120°, the validity is verified. If the default value is 10°, the channel is determined to be abnormal (e.g., there is interference or sampling failure), and the abnormal channel flag is triggered. The power frequency coupling signal of the channel will not participate in the current identification.

[0116] Step S2: Identification of equivalent circuit parameters of the live indicator based on power frequency response.

[0117] Using the power frequency excitation-response pair as input, the parameter identification equations of the high-frequency equivalent circuit (i.e., equivalent circuit) of the charged indicator are established, and the initial equivalent coupling capacitance of each channel is solved by nonlinear least squares fitting. Series inductor Loss resistance Key parameters, etc.

[0118] Step S21: Model the high-frequency equivalent circuit of the charged indicator.

[0119] The high-frequency equivalent circuit of the live indicator connected to the m-th channel is modeled as a series LCR network: the equivalent coupling capacitance (i.e., the initial equivalent coupling capacitance) is capacitively coupled to the high-voltage conductor; the equivalent series inductance (i.e., the series inductance) is generated by the leads and internal windings; the equivalent loss resistance (i.e., the loss resistance) includes the insulation dielectric loss and the lead resistance. The equivalent impedance of this network is... for:

[0120]

[0121] in, Let f be the equivalent impedance of the m-th channel at frequency f. The equivalent loss resistance (i.e., loss resistance) of the high-frequency equivalent circuit of the live indicator connected to the m-th channel. The equivalent series inductance (i.e., series inductance) of the high-frequency equivalent circuit of the live indicator connected to the m-th channel. Let f be the equivalent coupling capacitance (i.e., the initial equivalent coupling capacitance) of the high-frequency equivalent circuit of the charged indicator connected to the m-th channel, and f be the frequency of the signal.

[0122] Step S22: Establish the power frequency response equation.

[0123] In power frequency Under Hz conditions, the open-circuit output voltage amplitude (i.e., fundamental frequency amplitude) at the leads of the live indicator. With the power frequency voltage amplitude of high voltage conductors The relationship between them is determined by capacitive voltage division. The input impedance of the acquisition circuit... Connecting it in series with the equivalent circuit, the power frequency response equation is established:

[0124]

[0125] in, This is the equivalent impedance of a live indicator at power frequency. This is the lead wire transmission loss factor.

[0126] Step S23, equivalent capacitance Self-identification calculation.

[0127] Because the inductive and capacitive reactances at power frequency are much greater than the input impedance of the acquisition circuit. The power frequency response equation can be simplified to a purely capacitive voltage divider model, thus allowing for direct solution. :

[0128]

[0129] Step S24, series inductor and loss resistance Identification.

[0130] The high-frequency background noise signal (i.e., the background noise signal, which is collected during the non-PD discharge period within the detection window) is used as a broadband excitation, and the resonant frequency of the equivalent circuit is identified by power spectral density estimation. And thus, it can be deduced The resonant frequency of the high-frequency equivalent circuit of the charged indicator connected to the m-th channel. for:

[0131]

[0132] in, The peak value is determined by estimating the power spectral density of the background noise signal.

[0133] In determining Afterwards, combined Determine the channel's loss resistance based on the channel's quality factor. .

[0134] Step S25: Estimation of background noise power spectral density and identification of resonant frequency.

[0135] During the silent period without PD discharge (determined by threshold detection), the power spectral density estimate of the background noise signal of the m-th channel is calculated using the Welch method. :

[0136]

[0137] in, It is the Welch power spectral density estimate of the background noise signal in the m-th channel; The total number of Welch segments; For Hamming window functions; is the k-th segment of the background noise signal in the m-th channel; N is the number of signal points in each segment of the background noise signal.

[0138] Step S3: Calculate the broadband frequency response compensation function for each channel.

[0139] Based on the identified equivalent circuit parameters, the frequency response function (i.e., the frequency response represented in functional form) of each channel in the detection frequency band of 250kHz to 100MHz is calculated, and compared with the frequency response function of the reference channel to construct the frequency response compensation function of each channel.

[0140] Step S31: Initial equivalent coupling capacitance is updated via sliding.

[0141] Updated once per power frequency cycle The identification value (i.e., the initial equivalent coupling capacitance) is updated using an exponentially weighted moving average (EWMA) method to achieve online tracking of the aging drift of the charged indicator, thus obtaining the target equivalent coupling capacitance of the high-frequency equivalent circuit of the charged indicator connected to the m-th channel:

[0142]

[0143] in, This is the estimated target equivalent coupling capacitance value for the m-th channel after EWMA update for the d-th power frequency cycle; The target equivalent coupling capacitance (i.e., the historical equivalent coupling capacitance of the m-th channel in the previous cycle before the d-th power frequency cycle) is estimated after EWMA update for d-1 power frequency cycles. For the d-th power frequency cycle, the initial equivalent coupling capacitance corresponding to the m-th channel is obtained based on the power frequency response; It is a forgetting factor.

[0144] Step S32: Calculate the frequency response function of each channel.

[0145] Based on the obtained parameter set { , , } Calculate the equivalent impedance corresponding to the m-th channel. Then, the frequency response function between the open-circuit output voltage of the m-th channel at frequency f and the input PD excitation current is obtained. for:

[0146]

[0147] in, Let f be the frequency response function of the m-th channel, describing the amplitude-frequency and phase-frequency characteristics of the PD excitation signal after coupling through the charged indicator at the acquisition end; Let f be the input impedance of the m-th channel acquisition circuit at frequency f; The amplitude response of m channels at frequency f reflects the coupling gain of the channel to the PD pulse signal at that frequency.

[0148] Step S33: Select the reference channel and calculate the frequency response compensation function.

[0149] The channel with the highest signal-to-noise ratio is taken as the reference channel (numbered ref), and its frequency response function is denoted as... The frequency response compensation function of the remaining channels relative to the reference channel. Defined as:

[0150]

[0151] in, Let be the frequency response compensation function of the m-th channel relative to the reference channel, which is the core conversion coefficient for calibrating the PD pulse signal of each channel. When m = 1 (i.e., m is the reference channel), no compensation is needed; when | When |>1, it indicates that the coupling gain of the m-th channel to this frequency component is lower than that of the reference channel, requiring amplification compensation; when | Attenuation compensation is required when |<1; It also includes phase compensation to correct phase response differences between channels and ensure the alignment accuracy of the partial discharge pulse signal waveform.

[0152] Step S4: Real-time consistency calibration of multi-channel PD pulse signals.

[0153] The original PD pulse signals acquired from each channel are compared with the frequency response compensation function of the corresponding channel in the frequency domain. Multiplication completes frequency response compensation, outputting the normalized time-domain calibration signal (i.e., the target calibration signal) of each channel, eliminating the difference in coupling coefficients between channels and frequency response distortion.

[0154] Step S41: Frequency domain transformation of PD pulse signal.

[0155] The raw PD pulse signal acquired by the m-th channel within the PD detection window Perform a Fast Fourier Transform (FFT) to obtain the frequency domain signal. :

[0156]

[0157] in, Let N be the spectrum (i.e., frequency domain signal) of the PD pulse signal of the m-th channel, where N is the number of FFT points and n is the sampling point number, n = 0, 1, 2, ..., N-1.

[0158] Step S42, frequency domain compensation and inverse transform.

[0159] Will With the corresponding frequency response compensation function The signals are multiplied to complete frequency response compensation, and then subjected to inverse Fourier transform (IFFT) to recover the calibrated time-domain calibration signal (i.e., the target calibration signal). :

[0160]

[0161] in, Let m be the time-domain calibration signal of the m-th channel after frequency response compensation, and let each channel be normalized to the reference channel response; The frequency domain calibration signal corresponding to the m-th channel.

[0162] Step S43: Calculate the channel amplitude normalization coefficient (i.e., the normalization coefficient).

[0163] Based on the target equivalent coupling capacitance identified in each channel and updated by EWMA Calculate the static amplitude normalization coefficient of each channel relative to the reference channel. :

[0164]

[0165] in, This is the amplitude normalization coefficient corresponding to the m-th channel; The target equivalent coupling capacitance of the reference channel.

[0166] Step S5: Quantitative calculation of equivalent discharge quantity.

[0167] Calculate the equivalent discharge quantity of each channel based on the normalized calibration signal of each channel. :

[0168]

[0169]

[0170] in, Let be the equivalent discharge quantity of the m-th channel. Let be the input capacitor of the m-th channel acquisition circuit. Let m be the normalized calibration signal for the m-th channel. The duration of a single PD pulse signal.

[0171] The above optional implementation methods achieve at least the following effects:

[0172] (A) The power frequency coupling signal of the live indicator is used as a built-in calibration reference source to achieve channel consistency calibration with zero peripherals. This application discovers and utilizes the core physical mechanism of the live indicator: its power frequency sensing function and PD pulse coupling function share the same capacitive coupling path, which means that the power frequency response carries complete coupling coefficient information. Redefining the power frequency, which is usually considered to need to be filtered out, as a built-in calibration excitation is the fundamental innovation of this application, which distinguishes it from all existing TEV (Transient Earth Voltage) / pulse coupling calibration techniques, and fundamentally solves the engineering practicality defects of the external standard source method.

[0173] (B) Automatic identification of equivalent circuit parameters of multi-channel charged indicators was achieved, and a complete wideband calibration system was established. Through a three-step cascaded identification scheme of low-frequency capacitive voltage divider identification, background noise spectrum estimation identification, and resonance peak quality factor identification, the equivalent circuit parameters of the charged indicator LCR were completely extracted, and a frequency response compensation function covering the entire detection frequency band from 250kHz to 100MHz was constructed. This not only corrected the difference in absolute coupling coefficients but also eliminated frequency-related waveform distortion, making the wideband pulse waveform comparable across channels and providing a consistent signal quality basis for subsequent PRPD spectrum analysis and discharge type identification.

[0174] (C) This application achieves quantitative measurement capability of multi-channel equivalent discharge quantity, filling the technological gap in quantitative detection of pulse coupling for charged indicators. Existing pulse coupling detection schemes for charged indicators can only output relative amplitude comparison results and cannot provide an absolute quantitative value of the equivalent discharge quantity. This application achieves quantitative measurement of the equivalent discharge quantity using a charged indicator as a sensor by identifying the initial equivalent coupling capacitance online and establishing a conversion relationship with the equivalent discharge quantity. The error target is ≤±10%, greatly expanding the practical value of pulse coupling detection equipment.

[0175] (D) It has the ability to track the long-term drift of the coupling characteristics of the live indicator online, ensuring the long-term stability of the detection accuracy. Based on the EWMA sliding update mechanism, the initial equivalent coupling capacitance parameter estimate of each channel is automatically updated in each power frequency cycle. It can track the slow drift of the coupling characteristics caused by the aging of the live indicator (moisture absorption, thermal aging, mechanical deformation, etc.) without manual intervention, ensuring the quantitative accuracy of the detection device throughout its entire life cycle.

[0176] It should be noted that the steps shown in the flowchart in the accompanying drawings can be executed in a computer system such as a set of computer-executable instructions, and although a logical order is shown in the flowchart, in some cases the steps shown or described may be executed in a different order than that shown here.

[0177] This embodiment also provides an equivalent discharge quantity determination device, which is used to implement the above embodiments and preferred embodiments, and will not be repeated as already described. As used below, the terms "module" and "device" can refer to a combination of software and / or hardware that implements a predetermined function. Although the device described in the following embodiments is preferably implemented in software, hardware implementation, or a combination of software and hardware, is also possible and contemplated.

[0178] According to an embodiment of this application, an apparatus embodiment for implementing the equivalent discharge quantity determination method is also provided. Figure 3 This is a schematic diagram of an equivalent discharge quantity determination device according to an embodiment of this application, as shown below. Figure 3 As shown, the above-mentioned equivalent discharge quantity determination device includes a data acquisition module 302, a first determination module 304, a consistency calibration module 306, and a second determination module 308. The device will be described below.

[0179] The data acquisition module 302 is used to acquire multi-dimensional signals corresponding to multiple channels within the target period. The multi-dimensional signals include the power frequency coupling signal output by the live indicator connected to the corresponding channel, the background noise signal, and the partial discharge pulse signal.

[0180] The first determining module 304, connected to the data acquisition module 302, is used to determine the frequency response compensation for each of the multiple channels based on the multidimensional signals corresponding to the multiple channels respectively. The frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to the reference channel, and the reference channel is determined based on the signal-to-noise ratio of the multiple channels respectively.

[0181] The consistency calibration module 306 is connected to the first determination module 304 and is used to perform consistency calibration on the partial discharge pulse signals in the multidimensional signals corresponding to multiple channels based on the frequency response compensation corresponding to multiple channels respectively, so as to obtain the target calibration signals corresponding to multiple channels respectively.

[0182] The second determining module 308 is connected to the consistency calibration module 306 and is used to determine the equivalent discharge quantity corresponding to each of the multiple channels based on the target calibration signals corresponding to the multiple channels respectively.

[0183] The equivalent discharge quantity determination device provided in this application embodiment, by setting a data acquisition module 302, a first determination module 304, a consistency calibration module 306, and a second determination module 308, achieves the purpose of determining the frequency response compensation corresponding to multiple channels based on the multi-dimensional signals corresponding to multiple channels respectively, and then performing consistency calibration on the partial discharge pulse signals of each channel. This achieves the technical effect of improving the accuracy of the equivalent discharge quantity determination result of the channel connected to the charged indicator by performing consistency calibration on the partial discharge pulse signals of each channel, thereby solving the technical problem of inaccurate determination result of the equivalent discharge quantity of the channel connected to the charged indicator in related technologies.

[0184] It should be noted that the above modules can be implemented by software or hardware. For example, for the latter, it can be implemented in the following ways: the above modules can be located in the same processor; or the above modules can be located in different processors in any combination.

[0185] It should be noted that the data acquisition module 302, the first determination module 304, the consistency calibration module 306, and the second determination module 308 mentioned above correspond to steps S102 to S108 in the embodiments. The instances and application scenarios implemented by the above modules and corresponding steps are the same, but are not limited to the content disclosed in the above embodiments. It should be noted that the above modules, as part of the device, can run in a computer terminal.

[0186] It should be noted that the optional or preferred implementation methods of this embodiment can be found in the relevant descriptions in the embodiments, and will not be repeated here.

[0187] The equivalent discharge quantity determination device described above may also include a processor and a memory. The data acquisition module 302, the first determination module 304, the consistency calibration module 306, the second determination module 308, etc. are all stored in the memory as program units, and the processor executes the program units stored in the memory to realize the corresponding functions.

[0188] The processor contains a core that retrieves the corresponding program unit from memory. One or more cores may be configured. Memory may include non-persistent memory in computer-readable media, random access memory (RAM), and / or non-volatile memory, such as read-only memory (ROM) or flash RAM. Memory includes at least one memory chip.

[0189] This application provides a non-volatile storage medium storing a program that, when executed by a processor, implements a method for determining the equivalent discharge quantity.

[0190] This application provides an electronic device. Figure 4 This is a structural diagram of an electronic device provided according to an embodiment of this application. For example... Figure 4 As shown, the electronic device may include: one or more ( Figure 4 (Only one is shown in the document) Processor 402, memory 404, memory controller, and peripheral interface, wherein the peripheral interface is connected to the radio frequency module, audio module, and display. The electronic device includes a processor, memory, and a program stored in the memory and executable on the processor. When the processor executes the program, it performs the following steps: acquiring multi-dimensional signals corresponding to multiple channels within a target period, wherein the multi-dimensional signals include power frequency coupling signals output by a live indicator connected to the corresponding channel, background noise signals, and partial discharge pulse signals; determining frequency response compensations for each of the multiple channels based on the multi-dimensional signals corresponding to the multiple channels, wherein the frequency response compensations describe the frequency response difference of the corresponding channel relative to a reference channel, the reference channel being determined based on the signal-to-noise ratios corresponding to the multiple channels; performing consistency calibration on the partial discharge pulse signals in the multi-dimensional signals corresponding to the multiple channels based on the frequency response compensations corresponding to the multiple channels, obtaining target calibration signals corresponding to the multiple channels; and determining the equivalent discharge quantity corresponding to the multiple channels based on the target calibration signals corresponding to the multiple channels. The device in this document may be a server, PC, etc.

[0191] This application also provides a computer program product, which, when executed on a data processing device, is suitable for executing an initialization program having the following method steps: acquiring multi-dimensional signals corresponding to multiple channels within a target period, wherein the multi-dimensional signals include power frequency coupling signals output by a live indicator connected to the corresponding channel, background noise signals, and partial discharge pulse signals; determining frequency response compensations corresponding to multiple channels based on the multi-dimensional signals corresponding to the multiple channels, wherein the frequency response compensations are used to describe the frequency response difference of the corresponding channel relative to a reference channel, and the reference channel is determined based on the signal-to-noise ratios corresponding to the multiple channels; performing consistency calibration on the partial discharge pulse signals in the multi-dimensional signals corresponding to the multiple channels based on the frequency response compensations corresponding to the multiple channels, to obtain target calibration signals corresponding to the multiple channels; and determining the equivalent discharge quantity corresponding to the multiple channels based on the target calibration signals corresponding to the multiple channels.

[0192] Those skilled in the art will understand that embodiments of this application can be provided as methods, systems, or computer program products. Therefore, this application can take the form of a completely hardware embodiment, a completely software embodiment, or an embodiment combining software and hardware aspects. Furthermore, this application can take the form of a computer program product embodied on one or more computer-usable storage media (including but not limited to disk storage, CD-ROM, optical storage, etc.) containing computer-usable program code.

[0193] This application is described with reference to flowchart illustrations and / or block diagrams of methods, apparatus (systems), and computer program products according to embodiments of this application. It will be understood that each block of the flowchart illustrations and / or block diagrams, and combinations of blocks in the flowchart illustrations and / or block diagrams, can be implemented by computer program instructions. These computer program instructions can be provided to a processor of a general-purpose computer, special-purpose computer, embedded processor, or other programmable data processing apparatus to produce a machine, such that the instructions, which execute via the processor of the computer or other programmable data processing apparatus, generate instructions for implementing the flowchart... Figure 1 One or more processes and / or boxes Figure 1 A device that provides the functions specified in one or more boxes.

[0194] These computer program instructions may also be stored in a computer-readable storage medium that can direct a computer or other programmable data processing device to function in a particular manner, such that the instructions stored in the computer-readable storage medium produce an article of manufacture including instruction means, which are implemented in a process Figure 1 One or more processes and / or boxes Figure 1 The function specified in one or more boxes.

[0195] These computer program instructions may also be loaded onto a computer or other programmable data processing equipment to cause a series of operational steps to be performed on the computer or other programmable equipment to produce a computer-implemented process, thereby providing instructions that execute on the computer or other programmable equipment for implementing the process. Figure 1 One or more processes and / or boxes Figure 1 The steps of the function specified in one or more boxes.

[0196] In a typical configuration, a computing device includes one or more processors (CPU), input / output interfaces, network interfaces, and memory.

[0197] Memory may include non-persistent memory in computer-readable media, such as random access memory (RAM) and / or non-volatile memory, such as read-only memory (ROM) or flash RAM. Memory is an example of computer-readable media.

[0198] Computer-readable media includes both permanent and non-permanent, removable and non-removable media that can store information using any method or technology. Information can be computer-readable instructions, data structures, modules of programs, or other data. Examples of computer storage media include, but are not limited to, phase-change memory (PRAM), static random access memory (SRAM), dynamic random access memory (DRAM), other types of random access memory (RAM), read-only memory (ROM), electrically erasable programmable read-only memory (EEPROM), flash memory or other memory technologies, CD-ROM, digital versatile optical disc (DVD) or other optical storage, magnetic tape, magnetic disk storage or other magnetic storage devices, or any other non-transferable medium that can be used to store information accessible by a computing device. As defined herein, computer-readable media does not include transient computer-readable media, such as modulated data signals and carrier waves.

[0199] It should also be noted that the terms "comprising," "including," or any other variations thereof are intended to cover non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such process, method, article, or apparatus. Unless otherwise specified, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, method, article, or apparatus that includes that element.

[0200] Those skilled in the art will understand that embodiments of this application can be provided as methods, systems, or computer program products. Therefore, this application can take the form of a completely hardware embodiment, a completely software embodiment, or an embodiment combining software and hardware aspects. Furthermore, this application can take the form of a computer program product embodied on one or more computer-usable storage media (including, but not limited to, disk storage, CD-ROM, optical storage, etc.) containing computer-usable program code.

[0201] The above are merely embodiments of this application and are not intended to limit the scope of this application. Various modifications and variations can be made to this application by those skilled in the art. Any modifications, equivalent substitutions, improvements, etc., made within the spirit and principles of this application should be included within the scope of the claims of this application.

Claims

1. A method for determining equivalent discharge quantity, characterized in that, include: Acquire multi-dimensional signals corresponding to multiple channels within the target period, wherein the multi-dimensional signals include power frequency coupling signals output by the live indicator connected to the corresponding channel, background noise signals, and partial discharge pulse signals; Based on the multidimensional signals corresponding to the multiple channels, the frequency response compensation corresponding to the multiple channels is determined, wherein the frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to the reference channel, and the reference channel is determined based on the signal-to-noise ratio corresponding to the multiple channels. Based on the frequency response compensation corresponding to each of the multiple channels, the partial discharge pulse signal in the multidimensional signal corresponding to each of the multiple channels is subjected to consistency calibration to obtain the target calibration signal corresponding to each of the multiple channels. Based on the target calibration signals corresponding to the multiple channels, the equivalent discharge quantity corresponding to each of the multiple channels is determined.

2. The method according to claim 1, characterized in that, The step of determining the frequency response compensation for each of the multiple channels based on the multidimensional signals corresponding to each of the multiple channels includes: Based on the multidimensional signals corresponding to the multiple channels respectively, the parameter sets corresponding to the multiple channels are determined, wherein the parameter sets include the target equivalent coupling capacitance, series inductance and loss resistance of the equivalent circuit of the live indicator connected to the corresponding channel; Based on the parameter sets corresponding to the multiple channels respectively, the frequency response corresponding to the multiple channels is determined, wherein the frequency response is used to characterize the amplitude-frequency characteristics and phase-frequency characteristics of the corresponding channel to the partial discharge pulse signal; The channel with the highest signal-to-noise ratio among the multiple channels is determined as the reference channel; The ratio between the frequency response of the reference channel and the frequency response of each of the plurality of channels is determined as the frequency response compensation for each of the plurality of channels.

3. The method according to claim 2, characterized in that, The step of determining the parameter sets corresponding to the multiple channels based on the multidimensional signals corresponding to the multiple channels includes: Based on the power frequency coupling signal in the multidimensional signal corresponding to the multiple channels, the fundamental amplitude value corresponding to the multiple channels is determined. Based on the background noise signal in the multidimensional signal corresponding to each of the multiple channels, the resonant frequency corresponding to each of the multiple channels is determined. The resonant frequency is used to characterize the frequency point at which the amplitude-frequency response of the equivalent circuit of the live indicator connected to the corresponding channel reaches a peak within a preset frequency band. Based on the fundamental amplitude and resonant frequency corresponding to each of the multiple channels, the parameter sets corresponding to each of the multiple channels are determined.

4. The method according to claim 3, characterized in that, The step of determining the parameter set corresponding to each of the multiple channels based on the fundamental amplitude and the resonant frequency of each of the multiple channels includes: Based on the fundamental amplitude values ​​corresponding to the multiple channels, the initial equivalent coupling capacitance corresponding to the multiple channels is determined. Based on the initial equivalent coupling capacitance corresponding to each of the multiple channels and the resonant frequency corresponding to each of the multiple channels, the series inductance corresponding to each of the multiple channels is determined. Based on the initial equivalent coupling capacitance corresponding to each of the multiple channels and the series inductance corresponding to each of the multiple channels, the loss resistance corresponding to each of the multiple channels is determined. The initial equivalent coupling capacitances corresponding to the multiple channels are corrected to obtain the target equivalent coupling capacitances corresponding to the multiple channels. Based on the series inductance corresponding to each of the multiple channels, the loss resistance corresponding to each of the multiple channels, and the target equivalent coupling capacitance corresponding to each of the multiple channels, the parameter set corresponding to each of the multiple channels is determined.

5. The method according to claim 4, characterized in that, The step of correcting the initial equivalent coupling capacitance corresponding to each of the plurality of channels to obtain the target equivalent coupling capacitance corresponding to each of the plurality of channels includes: Obtain the historical equivalent coupling capacitance of each of the multiple channels in the previous cycle before the target cycle; Based on the historical equivalent coupling capacitances corresponding to the multiple channels, the initial equivalent coupling capacitances corresponding to the multiple channels are corrected to obtain the target equivalent coupling capacitances corresponding to the multiple channels.

6. The method according to claim 1, characterized in that, The step of performing consistency calibration on the partial discharge pulse signals in the multidimensional signals corresponding to the multiple channels based on the frequency response compensation of the multiple channels respectively, to obtain the target calibration signals corresponding to the multiple channels respectively, includes: The partial discharge pulse signals in the multidimensional signals corresponding to the multiple channels are respectively subjected to frequency domain transformation to obtain the frequency domain signals corresponding to the multiple channels respectively. Based on the frequency response compensation corresponding to each of the multiple channels and the frequency domain signals corresponding to each of the multiple channels, the frequency domain calibration signals corresponding to each of the multiple channels are obtained. The frequency domain calibration signals corresponding to the multiple channels are inversely transformed to obtain the target calibration signals corresponding to the multiple channels.

7. The method according to any one of claims 1 to 6, characterized in that, The step of determining the equivalent discharge quantity corresponding to each of the multiple channels based on the target calibration signals corresponding to each of the multiple channels includes: The ratio between the target equivalent coupling capacitance of the reference channel and the target equivalent coupling capacitance of each of the plurality of channels is determined as the normalization coefficient corresponding to each of the plurality of channels. Based on the normalization coefficients corresponding to the multiple channels and the target calibration signals corresponding to the multiple channels, the normalized calibration signals corresponding to the multiple channels are obtained. Based on the normalized calibration signals corresponding to the multiple channels respectively, and the target equivalent coupling capacitance of the reference channel, the equivalent discharge quantity corresponding to the multiple channels is determined.

8. A device for determining equivalent discharge quantity, characterized in that, include: The data acquisition module is used to acquire multi-dimensional signals corresponding to multiple channels within the target period, wherein the multi-dimensional signals include power frequency coupling signals output by the live indicator connected to the corresponding channel, background noise signals, and partial discharge pulse signals; The first determining module is used to determine the frequency response compensation corresponding to each of the multiple channels based on the multidimensional signals corresponding to each of the multiple channels, wherein the frequency response compensation is used to describe the frequency response difference of the corresponding channel relative to the reference channel, and the reference channel is determined based on the signal-to-noise ratio corresponding to each of the multiple channels. The consistency calibration module is used to perform consistency calibration on the partial discharge pulse signals in the multidimensional signals corresponding to the multiple channels based on the frequency response compensation corresponding to the multiple channels respectively, so as to obtain the target calibration signals corresponding to the multiple channels respectively. The second determining module is used to determine the equivalent discharge quantity corresponding to each of the multiple channels based on the target calibration signals corresponding to each of the multiple channels.

9. A non-volatile storage medium, characterized in that, The non-volatile storage medium stores multiple instructions, which are adapted to be loaded by a processor and executed by the equivalent discharge determination method according to any one of claims 1 to 7.

10. An electronic device, characterized in that, include: One or more processors and a memory, the memory being used to store one or more programs, wherein when the one or more programs are executed by the one or more processors, the one or more processors cause the one or more processors to implement the equivalent discharge quantity determination method according to any one of claims 1 to 7.

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