A 48v brushless gasoline pump based on phase voltage feedback adaptive dead-time compensation method

Abstract

This invention proposes an adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback. The method includes the following steps: S1, obtaining the actual phase voltage V_phase through a voltage sampling network at each phase output terminal, and comparing it with the reference voltage V_ref to obtain the dead-zone voltage error ΔV_observed; S2, dynamically calculating the dead-zone compensation amount ΔV_comp based on the phase current and the dead-zone voltage error ΔV_observed; S3, calculating the temperature correction coefficient K_T based on the ambient temperature, and performing temperature-adaptive correction on the compensation amount; S4, superimposing the corrected compensation amount onto the FOC voltage reference value and feeding it to the SVPWM modulator; S5, continuously monitoring after compensation and fine-tuning the compensation amount in a closed loop. This invention realizes a complete technical chain from voltage error observation, temperature adaptive compensation, current zero-crossing smoothing processing to closed-loop effect evaluation, significantly improving the current waveform quality, torque control accuracy, and system operational reliability of the 48V brushless gasoline pump over a wide speed, wide load, and wide temperature range, meeting the stringent requirements of automotive applications for high-performance fuel supply systems.

Description

Technical Field

[0001] This invention relates to the field of oil pump technology, and in particular to an adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback. Background Technology

[0002] With the accelerating pace of automotive electrification, 48V mild hybrid systems have become an important component of modern automotive powertrain architecture. Against this backdrop, the 48V brushless fuel pump, as a core actuator in the fuel supply system, directly impacts engine fuel economy and emissions performance through its drive control technology. Brushless DC motors (BLDC), with their high power density, high efficiency, long lifespan, and excellent speed regulation performance, have gradually replaced traditional brushed motors, becoming the preferred drive solution for 48V fuel pump systems. Summary of the Invention

[0003] This invention aims to at least solve the technical problems existing in the prior art, and in particular, it innovatively proposes an adaptive dead zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback.

[0004] To achieve the above-mentioned objectives of this invention, this invention provides an adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback, comprising the following steps:

[0005] S1. Obtain the actual phase voltage V_phase through the voltage sampling network at the output of each phase, compare it with the reference voltage V_ref, and obtain the dead zone voltage error ΔV_observed.

[0006] S2, dynamically calculate the dead zone compensation amount ΔV_comp based on the phase current and dead zone voltage error ΔV_observed;

[0007] S3, calculate the temperature correction coefficient K_T based on the ambient temperature, and perform temperature adaptive correction on the compensation amount;

[0008] S4, the corrected compensation amount is added to the FOC voltage reference value and fed to the SVPWM modulator;

[0009] S5, continuous monitoring after compensation, and closed-loop fine-tuning of the compensation amount.

[0010] In a preferred embodiment of the present invention, the expression for the dead zone voltage error in step S1 is:

[0011] ΔV_observed = V_ref - V_phase

[0012] Where ΔV_observed represents the dead zone voltage error;

[0013] V_ref represents the reference voltage;

[0014] V_phase represents the actual phase voltage.

[0015] In a preferred embodiment of the present invention, the method for calculating the actual phase voltage V_phase in step S1 is as follows:

[0016] V_phase=U_phase+R_phase1 / R_phase2×U_phase,

[0017] Where V_phase represents the actual phase voltage;

[0018] U_phase represents the phase voltage obtained by the drive controller;

[0019] R_phase1 represents the resistance value of resistor R_phase1;

[0020] R_phase2 represents the resistance value of resistor R_phase2;

[0021] phase represents the phase number, phase∈{u,v,w};

[0022] u represents phase u, v represents phase v, and w represents phase w;

[0023] When phase is u, the following is true:

[0024] V_u = U_u + R_u1 / R_u2 × U_u,

[0025] Where V_phase represents the actual u-phase voltage;

[0026] U_u represents the u-phase voltage obtained by the drive controller;

[0027] R_u1 represents the resistance value of resistor Ru1;

[0028] R_u2 represents the resistance value of resistor Ru2;

[0029] When phase is v, the following is true:

[0030] V_v = U_v + R_v1 / R_v2 × U_v,

[0031] Where V_phase represents the actual phase V voltage;

[0032] U_v represents the v-phase voltage obtained by the drive controller;

[0033] R_v1 represents the resistance value of resistor Rv1;

[0034] R_v2 represents the resistance value of resistor Rv2;

[0035] When phase is w, the following is true:

[0036] V_w = U_w + R_w1 / R_w2 × U_w,

[0037] Where V_phase represents the actual phase voltage of w;

[0038] U_w represents the w-phase voltage obtained by the drive controller;

[0039] R_w1 represents the resistance value of resistor Rw1;

[0040] R_w2 represents the resistance value of resistor Rw2.

[0041] In a preferred embodiment of the present invention, the method for calculating the dead zone compensation amount ΔV_comp in step S2 is as follows:

[0042] When i_phase > i_threshold:

[0043] ΔV_comp=ΔV_observed,

[0044] When i_phase<-i_threshold: ΔV_comp=-ΔV_observed,

[0045] When |i_phase| ≤ i_threshold: ΔV_comp = ΔV_observed × i_phase / i_threshold

[0046] Where i_phase represents the phase current;

[0047] ΔV_comp represents the dead zone compensation amount;

[0048] ΔV_observed represents the dead-zone voltage error;

[0049] || indicates taking the absolute value;

[0050] i_threshold represents the preset threshold value; it is set to 5% to 10% of the rated current.

[0051] In a preferred embodiment of the present invention, the expression for the temperature correction coefficient is:

[0052] K_T = 1 + α × (T_j - T_ref),

[0053] Where K_T represents the temperature correction factor;

[0054] α represents the temperature coefficient of the on-resistance of the field-effect transistor; it is taken as 0.004°C.

[0055] T_j represents the junction temperature with thermal resistance;

[0056] T_ref represents the reference temperature.

[0057] In a preferred embodiment of the present invention, the expression for the thermal resistance junction temperature is:

[0058] T_j = T_amb + P_loss × R_th_ja,

[0059] Where T_j represents the junction temperature of thermal resistance;

[0060] T_amb represents the acquired ambient temperature;

[0061] P_loss represents the heating power of the field-effect transistor;

[0062] R_th_ja represents the thermal resistance of the field-effect transistor.

[0063] In a preferred embodiment of the present invention, the expression for temperature-adaptive correction of the compensation amount is:

[0064] ΔV_comp_final=ΔV_comp×K_T,

[0065] Wherein, ΔV_comp_final represents the corrected compensation amount;

[0066] ΔV_comp represents the dead zone compensation amount;

[0067] K_T represents the temperature correction factor.

[0068] In a preferred embodiment of the present invention, the closed-loop adjustment evaluates the compensation effect by monitoring the peak-to-effective current ratio (CF) or the amplitude of the 5th or 7th current harmonics. When the CF or harmonic amplitude exceeds the threshold, the compensation amount is finely adjusted, and the fine-tuning frequency is once every 100ms.

[0069] The present invention also discloses a computer system, comprising:

[0070] processor;

[0071] Memory used to store processor-executable instructions;

[0072] The processor is configured to implement an adaptive dead-time compensation method for a 48V brushless gasoline pump based on phase voltage feedback when executing the executable instructions.

[0073] The present invention also discloses a computer-readable storage medium, comprising:

[0074] A memory on which computer programs are stored;

[0075] A processor is configured to execute the program in the memory to implement an adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback.

[0076] In summary, by adopting the above technical solutions, this invention realizes a complete technical chain from voltage error observation, temperature adaptive compensation, current zero-crossing smoothing processing to closed-loop effect evaluation, which significantly improves the current waveform quality, torque control accuracy and system operation reliability of the 48V brushless gasoline pump in a wide range of speeds, loads and temperatures, meeting the stringent requirements of automotive applications for high-performance fuel supply systems.

[0077] Additional aspects and advantages of the invention will be set forth in part in the description which follows, and in part will be obvious from the description, or may be learned by practice of the invention. Attached Figure Description

[0078] The above and / or additional aspects and advantages of the present invention will become apparent and readily understood from the description of the embodiments taken in conjunction with the following drawings, in which:

[0079] Figure 1 This is a schematic flowchart of the present invention. Detailed Implementation

[0080] Embodiments of the present invention are described in detail below. Examples of these embodiments are shown in the accompanying drawings, wherein the same or similar reference numerals denote the same or similar elements or elements having the same or similar functions throughout. The embodiments described below with reference to the accompanying drawings are exemplary and are only used to explain the present invention, and should not be construed as limiting the present invention.

[0081] This invention provides an adaptive dead-time compensation method for a 48V brushless gasoline pump based on phase voltage feedback, such as... Figure 1 As shown, it includes the following steps:

[0082] S1, the actual phase voltage V_phase is obtained through the voltage sampling network at the output of each phase, and compared with the reference voltage V_ref to obtain the dead zone voltage error ΔV_observed; the calculation expression for the reference voltage V_ref is:

[0083] V_ref=D×V_dc,

[0084] Where V_ref represents the reference voltage;

[0085] D represents the duty cycle of the current input;

[0086] V_dc represents the 48V power supply voltage;

[0087] S2, dynamically calculate the dead zone compensation amount ΔV_comp based on the phase current and dead zone voltage error ΔV_observed;

[0088] S3, calculate the temperature correction coefficient K_T based on the ambient temperature, and perform temperature adaptive correction on the compensation amount;

[0089] S4, the corrected compensation amount is added to the FOC voltage reference value and fed to the SVPWM modulator;

[0090] S5, after compensation, continue monitoring and fine-tune the compensation amount in a closed loop; or execute step S1.

[0091] In a preferred embodiment of the present invention, the expression for the dead zone voltage error in step S1 is:

[0092] ΔV_observed = V_ref - V_phase

[0093] Where ΔV_observed represents the dead zone voltage error;

[0094] V_ref represents the reference voltage;

[0095] V_phase represents the actual phase voltage.

[0096] In a preferred embodiment of the present invention, the method for calculating the actual phase voltage V_phase in step S1 is as follows:

[0097] V_phase=U_phase+R_phase1 / R_phase2×U_phase,

[0098] Where V_phase represents the actual phase voltage;

[0099] U_phase represents the phase voltage obtained by the drive controller;

[0100] R_phase1 represents the resistance value of resistor R_phase1;

[0101] R_phase2 represents the resistance value of resistor R_phase2;

[0102] phase represents the phase number, phase∈{u,v,w};

[0103] u represents phase u, v represents phase v, and w represents phase w;

[0104] When phase is u, the following is true:

[0105] V_u = U_u + R_u1 / R_u2 × U_u,

[0106] Where V_phase represents the actual u-phase voltage;

[0107] U_u represents the u-phase voltage obtained by the drive controller;

[0108] R_u1 represents the resistance value of resistor Ru1;

[0109] R_u2 represents the resistance value of resistor Ru2;

[0110] When phase is v, the following is true:

[0111] V_v = U_v + R_v1 / R_v2 × U_v,

[0112] Where V_phase represents the actual phase V voltage;

[0113] U_v represents the v-phase voltage obtained by the drive controller;

[0114] R_v1 represents the resistance value of resistor Rv1;

[0115] R_v2 represents the resistance value of resistor Rv2;

[0116] When phase is w, the following is true:

[0117] V_w = U_w + R_w1 / R_w2 × U_w,

[0118] Where V_phase represents the actual phase voltage of w;

[0119] U_w represents the w-phase voltage obtained by the drive controller;

[0120] R_w1 represents the resistance value of resistor Rw1;

[0121] R_w2 represents the resistance value of resistor Rw2.

[0122] In a preferred embodiment of the present invention, the method for calculating the dead zone compensation amount ΔV_comp in step S2 is as follows:

[0123] When i_phase > i_threshold:

[0124] ΔV_comp=ΔV_observed,

[0125] When i_phase<-i_threshold: ΔV_comp=-ΔV_observed,

[0126] When |i_phase| ≤ i_threshold: ΔV_comp = ΔV_observed × i_phase / i_threshold

[0127] Where i_phase represents the phase current;

[0128] ΔV_comp represents the dead zone compensation amount;

[0129] ΔV_observed represents the dead-zone voltage error;

[0130] || indicates taking the absolute value;

[0131] i_threshold represents the preset judgment threshold; it is taken as 5% to 10% of the rated current (3A), and here it is taken as 0.2A.

[0132] In a preferred embodiment of the present invention, the expression for the temperature correction coefficient is:

[0133] K_T = 1 + α × (T_j - T_ref),

[0134] Where K_T represents the temperature correction factor;

[0135] α represents the temperature coefficient of the on-resistance of the field-effect transistor; it is taken as 0.004°C.

[0136] T_j represents the junction temperature with thermal resistance;

[0137] T_ref represents the reference temperature.

[0138] In a preferred embodiment of the present invention, the expression for the thermal resistance junction temperature is:

[0139] T_j = T_amb + P_loss × R_th_ja,

[0140] Where T_j represents the junction temperature of thermal resistance;

[0141] T_amb represents the acquired ambient temperature;

[0142] P_loss represents the heating power of the field-effect transistor;

[0143] R_th_ja represents the thermal resistance of the field-effect transistor.

[0144] In a preferred embodiment of the present invention, the expression for temperature-adaptive correction of the compensation amount is:

[0145] ΔV_comp_final=ΔV_comp×K_T,

[0146] Wherein, ΔV_comp_final represents the corrected compensation amount;

[0147] ΔV_comp represents the dead zone compensation amount;

[0148] K_T represents the temperature correction factor.

[0149] In a preferred embodiment of the present invention, the closed-loop adjustment evaluates the compensation effect by monitoring the peak / effective current ratio or the amplitude of the 5th and 7th current harmonics. When the CF or harmonic amplitude exceeds the threshold, the compensation amount is finely adjusted, and the fine-tuning frequency is once every 100ms.

[0150] The present invention also discloses a computer system, comprising:

[0151] processor;

[0152] Memory used to store processor-executable instructions;

[0153] The processor is configured to implement an adaptive dead-time compensation method for a 48V brushless gasoline pump based on phase voltage feedback when executing the executable instructions.

[0154] The present invention also discloses a computer-readable storage medium, comprising:

[0155] A memory on which computer programs are stored;

[0156] A processor is configured to execute the program in the memory to implement an adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback.

[0157] The present invention also discloses a 48V brushless gasoline pump system, including a motor and a drive controller, and a drive module connected to the motor and the drive controller;

[0158] The drive module includes a u-phase drive module, a v-phase drive module, and a w-phase drive module;

[0159] The u-phase drive module includes:

[0160] The input power supply voltage terminal VB1 of the drive controller is connected to the first terminal of capacitor C39 and the first terminal of resistor R37 respectively;

[0161] The second terminal of resistor R37 is connected to the negative terminal of diode D13. The positive terminal of diode D13 is connected to the first terminal of capacitor C42 and the 12V power supply. The second terminal of capacitor C42 is connected to the power supply ground.

[0162] The drive signal output terminal HO1 of the drive controller is connected to the negative terminal of diode D7 and the first terminal of resistor R40, respectively.

[0163] The positive terminal of diode D7 is connected to the first terminal of resistor R41;

[0164] The second terminals of resistor R40 and resistor R41 are connected to the first terminal of capacitor U4, the negative terminal of unidirectional transient suppression diode D16, and the gate of field-effect transistor Q4, respectively.

[0165] The drain of the field-effect transistor Q4 is connected to the power supply VDD-48V;

[0166] The drive signal output terminal LO1 of the drive controller is connected to the negative terminal of diode D8 and the first terminal of resistor R42, respectively.

[0167] The positive terminal of diode D8 is connected to the first terminal of resistor R43;

[0168] The second terminals of resistor R42 and resistor R43 are connected to the first terminal of capacitor U5, the negative terminal of unidirectional transient suppression diode D17, and the gate of field-effect transistor Q5, respectively.

[0169] The source of the field-effect transistor Q5 is connected to the first terminal of the resistor R56;

[0170] The bias voltage terminal VS1 of the drive controller is connected to the second terminal of capacitor C39, the second terminal of capacitor U4, the positive terminal of unidirectional transient suppression diode D16, the source of field-effect transistor Q4, and the drain of field-effect transistor Q5, respectively; the source of field-effect transistor Q4 is the U-phase drive output terminal;

[0171] The second terminal of capacitor U5, the positive terminal of unidirectional transient suppression diode D17, and the second terminal of resistor R56 are respectively connected to the first terminal of resistor R59, and the second terminal of resistor R59 is connected to the power supply ground.

[0172] The v-phase drive module includes:

[0173] The input power supply voltage terminal VB2 of the drive controller is connected to the first terminal of capacitor C40 and the first terminal of resistor R38, respectively.

[0174] The second terminal of resistor R38 is connected to the cathode of diode D14. The anode of diode D14 is connected to the first terminal of capacitor C43 and the 12V power supply. The second terminal of capacitor C43 is connected to the power supply ground.

[0175] The drive signal output terminal HO2 of the drive controller is connected to the negative terminal of diode D9 and the first terminal of resistor R44, respectively.

[0176] The positive terminal of diode D9 is connected to the first terminal of resistor R45;

[0177] The second terminals of resistor R44 and resistor R45 are connected to the first terminal of capacitor U6, the cathode of unidirectional transient suppression diode D18, and the gate of field-effect transistor Q6, respectively.

[0178] The drain of the field-effect transistor Q6 is connected to the power supply VDD-48V;

[0179] The drive signal output terminal LO2 of the drive controller is connected to the negative terminal of diode D10 and the first terminal of resistor R46, respectively.

[0180] The positive terminal of diode D10 is connected to the first terminal of resistor R47;

[0181] The second terminals of resistor R46 and resistor R47 are connected to the first terminal of capacitor U7, the negative terminal of unidirectional transient suppression diode D19, and the gate of field-effect transistor Q7, respectively.

[0182] The source of the field-effect transistor Q7 is connected to the first terminal of the resistor R57;

[0183] The bias voltage terminal VS2 of the drive controller is connected to the second terminal of capacitor C40, the second terminal of capacitor U6, the positive terminal of unidirectional transient suppression diode D18, the source of field-effect transistor Q6, and the drain of field-effect transistor Q7, respectively; the source of field-effect transistor Q6 is the V-phase drive output terminal;

[0184] The second terminal of capacitor U7, the positive terminal of unidirectional transient suppression diode D19, and the second terminal of resistor R57 are respectively connected to the first terminal of resistor R59;

[0185] The w-phase drive module includes:

[0186] The input power supply voltage terminal VB3 of the drive controller is connected to the first terminal of capacitor C41 and the first terminal of resistor R39, respectively.

[0187] The second terminal of resistor R39 is connected to the cathode of diode D15. The anode of diode D15 is connected to the first terminal of capacitor C44 and the 12V power supply. The second terminal of capacitor C44 is connected to the power supply ground.

[0188] The drive signal output terminal HO3 of the drive controller is connected to the negative terminal of diode D11 and the first terminal of resistor R48, respectively.

[0189] The positive terminal of diode D11 is connected to the first terminal of resistor R49;

[0190] The second terminals of resistor R48 and resistor R49 are connected to the first terminal of capacitor U8, the negative terminal of unidirectional transient suppression diode D20, and the gate of field-effect transistor Q8, respectively.

[0191] The drain of the field-effect transistor Q8 is connected to the power supply VDD-48V;

[0192] The drive signal output terminal LO3 of the drive controller is connected to the negative terminal of diode D12 and the first terminal of resistor R50, respectively.

[0193] The positive terminal of diode D12 is connected to the first terminal of resistor R51;

[0194] The second terminals of resistor R50 and resistor R51 are connected to the first terminal of capacitor U9, the cathode of unidirectional transient suppression diode D21, and the gate of field-effect transistor Q9, respectively.

[0195] The source of the field-effect transistor Q9 is connected to the first terminal of the resistor R58;

[0196] The bias voltage terminal VS3 of the drive controller is connected to the second terminal of capacitor C41, the second terminal of capacitor U8, the positive terminal of unidirectional transient suppression diode D20, the source of field-effect transistor Q8, and the drain of field-effect transistor Q9, respectively; the source of field-effect transistor Q8 is the W-phase drive output terminal;

[0197] The second terminal of capacitor U9, the positive terminal of unidirectional transient suppression diode D21, and the second terminal of resistor R58 are respectively connected to the first terminal of resistor R59;

[0198] The power module includes:

[0199] The power supply terminal VCC and the power input terminal VIN of the drive controller are respectively connected to the first terminal of capacitor C37, the first terminal of capacitor C38, the first terminal of capacitor C35, the first terminal of capacitor C36, the first terminal of capacitor C22, the first terminal of capacitor C23, the first terminal of resistor R22, and the 12V power supply.

[0200] The second terminals of capacitors C37, C38, C35, C36, C22, and C23 are connected to the power supply ground.

[0201] The second terminal of resistor R22 is connected to the enable terminal INH / EN of the drive controller;

[0202] The power ground terminal GND of the drive controller is connected to the power ground.

[0203] The power output module includes:

[0204] The power input terminal H1 of the power interface is connected to the first terminal of the bidirectional transient suppression diode D22, the first terminal of the capacitor C1, and the first terminal of the inductor L1, respectively.

[0205] The second terminal of inductor L1 is connected to the first terminal of capacitor C3, the first terminal of resistor R1, the first terminal of capacitor U14, and the first terminal of inductor L8, respectively; the second terminal of inductor L1 outputs power supply VDD-48V.

[0206] The second terminal of capacitor C1 is connected to the first terminal of capacitor C2;

[0207] The second terminal of capacitor C3 is connected to the first terminal of capacitor C4;

[0208] The second end of resistor R1 is connected to the first end of resistor R3, the gate of field-effect transistor Q1, the negative terminal of unidirectional transient suppression diode D2, and the first end of capacitor C6, respectively.

[0209] The power input terminal H2 of the power interface is connected to the second terminal of the bidirectional transient suppression diode D22, the second terminal of capacitor C2, the second terminal of capacitor C4, the first terminal of capacitor C5, and the drain of the field-effect transistor Q1.

[0210] The second terminal of capacitor C5 is connected to the first terminal of resistor R2;

[0211] The source of the field-effect transistor Q1, the positive terminal of the unidirectional transient suppression diode D2, the second terminal of resistor R2, the second terminal of resistor R3, the second terminal of capacitor C6, and the second terminal of capacitor U14 are connected to the power supply ground respectively.

[0212] The second terminal of inductor L8 is connected to the first terminal of capacitor C45, the power supply terminal VIN of power chip U11, and the enable terminal EN / UVLO of power chip U11, respectively.

[0213] The second terminal of capacitor C45 is connected to the power ground terminal GND and the power ground of power chip U11, respectively.

[0214] The on terminal RON of the power chip U11 is connected to the first terminal of resistor R63, and the second terminal of resistor R63 is connected to the power ground.

[0215] The pad EP of the power chip U11 is connected to the power ground.

[0216] The switching node SW of the power chip U11 is connected to the first terminal of capacitor C46, ​​the first terminal of resistor R64, and the first terminal of inductor U13, respectively.

[0217] The second terminal of capacitor C46 is connected to the bootstrap terminal BST of power chip U11.

[0218] The second terminal of resistor R64 is connected to the first terminal of capacitor C47 and the first terminal of capacitor C48, respectively.

[0219] The second terminal of capacitor C48 is connected to the first terminal of resistor R65, the first terminal of resistor R66, and the feedback terminal FB of power chip U11, respectively.

[0220] The second terminal of inductor U13 and the second terminal of capacitor C47 are respectively connected to the first terminal of capacitor C49, the first terminal of capacitor C50 and the second terminal of resistor R65; the second terminal of inductor U13 outputs 12V power.

[0221] The second terminals of capacitor C49, capacitor C50, and resistor R66 are connected to the power supply ground.

[0222] It also includes a bus module, which includes:

[0223] The bus terminal LIN of the drive controller is connected to the first terminal of capacitor C18 and the first terminal of bidirectional transient suppression diode D5, respectively.

[0224] The second terminal of capacitor C18 and the second terminal of bidirectional transient suppression diode D5 are connected to the power supply ground, respectively; the bus terminal LIN of the drive controller is the data terminal;

[0225] It also includes an input voltage sampling module, which includes:

[0226] The voltage acquisition terminal ADC_CH7 / P0.3 of the drive controller is connected to the first terminal of resistor R5, the first terminal of resistor R7, and the first terminal of capacitor C11, respectively.

[0227] The second terminal of resistor R5 is connected to the power supply VDD-48V;

[0228] The second terminal of resistor R7 and the second terminal of capacitor C11 are connected to the power supply ground, respectively.

[0229] It also includes a serial port module, which includes:

[0230] The data terminal SWDIO / P2.4 of the drive controller is connected to the data terminal of the serial interface;

[0231] The clock input SWCLK of the drive controller is connected to the clock input of the serial port interface;

[0232] The power supply terminal of the serial port interface is connected to the external power supply terminal AVDD of the drive controller, the first terminal of capacitor C24, and the first terminal of capacitor C25; the external power supply terminal AVDD of the drive controller outputs 5V power.

[0233] The power ground terminal of the serial port interface is connected to the power ground.

[0234] The second terminals of capacitors C24 and C25 are connected to the power supply ground, respectively.

[0235] The external power wake-up terminal WAKE_N of the drive controller is connected to the first terminal of resistor R31, and the second terminal of resistor R31 is connected to the power ground.

[0236] It also includes a reset module, which includes:

[0237] The reset terminal RSTN / P0.2 of the drive controller is connected to the first terminal of resistor R17, the first terminal of capacitor C20, and the first terminal of the reset button, respectively.

[0238] The second terminal of resistor R17 is connected to the 5V power supply;

[0239] The second terminal of capacitor C20 is connected to the power supply ground;

[0240] The second end of the reset button is connected to the power ground;

[0241] It also includes an output module, which includes:

[0242] The control terminal HALL_IN2 / P2.6 of the drive controller is connected to the first terminal of resistor R14;

[0243] The second end of resistor R14 is connected to the first end of resistor R13 and the gate of field-effect transistor Q2, respectively.

[0244] The drain of the field-effect transistor Q2 is connected to the first terminal of the resistor R9;

[0245] The second terminal of resistor R9 is connected to the first terminal of resistor R8 and the second terminal of bidirectional transient suppression diode D31, respectively; the first terminal of resistor R8 is the output terminal.

[0246] The second terminal of resistor R8 is connected to the power supply VDD-48V;

[0247] The second terminal of resistor R13, the source of field-effect transistor Q2, and the second terminal of bidirectional transient suppression diode D31 are connected to the power supply ground, respectively.

[0248] It also includes an input module, which includes:

[0249] The data terminal ADC_CH8 / P0.4 of the drive controller is connected to the first terminal of resistor R21, the first terminal of capacitor C29, and the source of field-effect transistor Q3;

[0250] The second terminal of resistor R21 is connected to the first terminal of capacitor C26 and the 5V power supply, respectively. The second terminal of capacitor C26 is connected to the power supply ground.

[0251] The gate of the field-effect transistor Q3 is connected to the first terminal of resistor R16 and the first terminal of resistor R20, respectively.

[0252] The second terminal of resistor R20, the source of field-effect transistor Q3, and the second terminal of capacitor C29 are connected to the power supply ground, respectively.

[0253] The second end of resistor R16 is connected to the first end of resistor R12 and the first end of resistor R15, respectively.

[0254] The second terminal of resistor R15 is connected to the cathode of diode D6, and the anode of diode D6 is connected to the power supply VDD-48V; the second terminal of resistor R15 is the output terminal.

[0255] The second terminal of resistor R12 is connected to the first terminal of bidirectional transient suppression diode D32, and the second terminal of bidirectional transient suppression diode D32 is connected to the power supply ground;

[0256] It also includes an indicator module, which includes:

[0257] The indicator terminal P2.12 of the drive controller is connected to the first terminal of resistor R62;

[0258] The second terminal of resistor R62 is connected to the first terminal of indicator LED1;

[0259] The second terminal of indicator LED1 is connected to the power ground;

[0260] It also includes an overcurrent sampling module, and the current sampling module includes:

[0261] The overcurrent sampling terminal ADC_CH15 / P0.11 of the drive controller is connected to the first terminal of resistor R27 and the first terminal of capacitor C30;

[0262] The second terminal of capacitor C30 is connected to the first terminal of resistor R23 and the power supply ground, respectively.

[0263] The second terminals of resistors R23 and R27 are respectively connected to the second terminal of resistor R58;

[0264] It also includes an encoder module, which includes:

[0265] The SPI clock pin ADC_CH14 / P2.1 of the drive controller is connected to the clock pin of the encoder interface;

[0266] The SPI data output terminals P0.15 / OSC_OUT / P3.9 of the drive controller are connected to the data input terminals of the encoder interface;

[0267] The SPI data input terminals P1.0, OSC_IN, and P2.8 of the drive controller are connected to the data output terminals of the encoder interface;

[0268] The ground terminal of the encoder interface is connected to the power ground.

[0269] It also includes a current sampling module, which includes a U-phase current sampling module, a V-phase current sampling module, and a W-phase current sampling module;

[0270] The u-phase current sampling module includes:

[0271] The current sampling terminal OPA1_IP / P3.0 of the drive controller is connected to the first terminal of capacitor C34 and the first terminal of resistor R32, respectively.

[0272] The current sampling terminal OPA1_IN / P3.1 of the drive controller is connected to the second terminal of capacitor C34 and the first terminal of resistor R34, respectively.

[0273] The second terminal of resistor R32 is connected to the first terminal of resistor R56, and the second terminal of resistor R34 is connected to the second terminal of resistor R56.

[0274] The phase v current sampling module includes:

[0275] The current sampling terminal OPA0_IP / P3.5 of the drive controller is connected to the first terminal of capacitor C33 and the first terminal of resistor R30, respectively.

[0276] The current sampling terminals OPA0_IN and P3.7 of the drive controller are connected to the second terminal of capacitor C33 and the first terminal of resistor R36, respectively.

[0277] The second terminal of resistor R30 is connected to the first terminal of resistor R57, and the second terminal of resistor R36 is connected to the second terminal of resistor R57.

[0278] The w-phase current sampling module includes:

[0279] The current sampling terminal OPA2_IP / P3.10 of the drive controller is connected to the first terminal of capacitor C32 and the first terminal of resistor R35, respectively;

[0280] The current sampling terminals P2.9 / OPA2_IN / P3.11 of the drive controller are connected to the second terminal of capacitor C32 and the first terminal of resistor R33, respectively;

[0281] The second terminal of resistor R35 is connected to the first terminal of resistor R58, and the second terminal of resistor R33 is connected to the second terminal of resistor R58.

[0282] It also includes a bus current sampling module, which includes:

[0283] The current sampling terminal OPA3_IP / P3.15 of the drive controller is connected to the first terminal of capacitor C31 and the first terminal of resistor R29, respectively;

[0284] The current sampling terminal OPA3_IN / P3.14 of the drive controller is connected to the second terminal of capacitor C31 and the first terminal of resistor R28, respectively.

[0285] The second terminal of resistor R29 is connected to the first terminal of resistor R59, and the second terminal of resistor R28 is connected to the second terminal of resistor R59.

[0286] It also includes a voltage sampling network, which includes a u-phase voltage sampling network, a v-phase voltage sampling network, and a w-phase voltage sampling network;

[0287] The u-phase voltage sampling network includes:

[0288] The first terminal of resistor Ru1 is connected to the source of field-effect transistor Q4;

[0289] The second end of resistor Ru1 is connected to the first end of resistor Ru2 and the first end of resistor Ru3;

[0290] The second terminal of resistor Ru2 is connected to the power supply ground;

[0291] The second end of resistor Ru3 is connected to the first end of capacitor Cu1 and the voltage sampling terminal CAN_RX / P0.12 of the drive controller, respectively;

[0292] The second terminal of capacitor Cu1 is connected to the power supply ground.

[0293] The phase-v voltage sampling network includes:

[0294] The first terminal of resistor Ru1 is connected to the source of field-effect transistor Q4;

[0295] The second end of resistor Ru1 is connected to the first end of resistor Ru2 and the first end of resistor Ru3;

[0296] The second terminal of resistor Ru2 is connected to the power supply ground;

[0297] The second end of resistor Ru3 is connected to the first end of capacitor Cu1 and the voltage sampling terminal CAN_RX / P0.12 of the drive controller, respectively;

[0298] The second terminal of capacitor Cu1 is connected to the power supply ground; the resistance values ​​of resistors Ru1, Ru2 and Ru3 are 47KΩ, 3.3KΩ and 100Ω respectively, and the capacitance value of capacitor Cu1 is 1nF.

[0299] The first terminal of resistor Rv1 is connected to the source of field-effect transistor Q6;

[0300] The second terminal of resistor Rv1 is connected to the first terminals of resistors Rv2 and Rv3.

[0301] The second terminal of resistor Rv2 is connected to the power supply ground;

[0302] The second end of resistor Rv3 is connected to the first end of capacitor Cv1 and the voltage sampling terminal CAN_TX / P0.13 of the drive controller, respectively;

[0303] The second terminal of capacitor Cv1 is connected to the power supply ground; the resistance values ​​of resistors Rv1, Rv2 and Rv3 are 47KΩ, 3.3KΩ and 100Ω respectively, and the capacitance value of capacitor Cv1 is 1nF.

[0304] The phase voltage sampling network includes:

[0305] The first terminal of resistor Rw1 is connected to the source of field-effect transistor Q8;

[0306] The second terminal of resistor Rw1 is connected to the first terminals of resistors Rw2 and Rw3;

[0307] The second terminal of resistor Rw2 is connected to the power supply ground;

[0308] The second terminal of resistor Rw3 is connected to the first terminal of capacitor Cw1 and the voltage sampling terminal CMP0_IP4 / P0.14 of the drive controller, respectively.

[0309] The second terminal of capacitor Cw1 is connected to the power supply ground; the resistance values ​​of resistors Rw1, Rw2 and Rw3 are 47KΩ, 3.3KΩ and 100Ω respectively, and the capacitance value of capacitor Cw1 is 1nF.

[0310] Although embodiments of the invention have been shown and described, those skilled in the art will understand that various changes, modifications, substitutions and alterations can be made to these embodiments without departing from the principles and spirit of the invention, the scope of which is defined by the claims and their equivalents.

Claims

1. An adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback, characterized in that, Includes the following steps: S1. Obtain the actual phase voltage V_phase through the voltage sampling network at the output of each phase, compare it with the reference voltage V_ref, and obtain the dead zone voltage error ΔV_observed. S2, dynamically calculate the dead zone compensation amount ΔV_comp based on the phase current and dead zone voltage error ΔV_observed; S3, calculate the temperature correction coefficient K_T based on the ambient temperature, and perform temperature adaptive correction on the compensation amount; S4, the corrected compensation amount is added to the FOC voltage reference value and fed to the SVPWM modulator; S5, continuous monitoring after compensation, and closed-loop fine-tuning of the compensation amount.

2. The adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback according to claim 1, characterized in that, The expression for the dead-zone voltage error in step S1 is: ΔV_observed = V_ref - V_phase Where ΔV_observed represents the dead zone voltage error; V_ref represents the reference voltage; V_phase represents the actual phase voltage.

3. The adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback according to claim 1, characterized in that, The method for calculating the actual phase voltage V_phase in step S1 is as follows: V_phase=U_phase+R_phase1 / R_phase2×U_phase, Where V_phase represents the actual phase voltage; U_phase represents the phase voltage obtained by the drive controller; R_phase1 represents the resistance value of resistor R_phase1; R_phase2 represents the resistance value of resistor R_phase2.

4. The adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback according to claim 1, characterized in that, The method for calculating the dead zone compensation amount ΔV_comp in step S2 is as follows: When i_phase > i_threshold: ΔV_comp=ΔV_observed, When i_phase<-i_threshold: ΔV_comp=-ΔV_observed, When |i_phase| ≤ i_threshold: ΔV_comp = ΔV_observed × i_phase / i_threshold Where i_phase represents the phase current; ΔV_comp represents the dead zone compensation amount; ΔV_observed represents the dead-zone voltage error; || indicates taking the absolute value; i_threshold represents the preset threshold for judgment.

5. The adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback according to claim 1, characterized in that, The expression for the temperature correction factor is: K_T = 1 + α × (T_j - T_ref), Where K_T represents the temperature correction factor; α represents the temperature coefficient of the on-resistance of the field-effect transistor; T_j represents the junction temperature with thermal resistance; T_ref represents the reference temperature.

6. The adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback according to claim 1, characterized in that, The expression for the junction temperature with thermal resistance is: T_j = T_amb + P_loss × R_th_ja, Where T_j represents the junction temperature of thermal resistance; T_amb represents the acquired ambient temperature; P_loss represents the heating power of the field-effect transistor; R_th_ja represents the thermal resistance of the field-effect transistor.

7. The adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback according to claim 1, characterized in that, The expression for temperature-adaptive correction of the compensation amount is: ΔV_comp_final=ΔV_comp×K_T, Wherein, ΔV_comp_final represents the corrected compensation amount; ΔV_comp represents the dead zone compensation amount; K_T represents the temperature correction factor.

8. A computer system, characterized in that, include: processor; Memory used to store processor-executable instructions; The processor is configured to implement the adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback as described in any one of claims 1 to 7 when executing the executable instructions.

9. A computer-readable storage medium, characterized in that, include: A memory on which computer programs are stored; A processor is configured to execute the program in the memory to implement the adaptive dead-zone compensation method for a 48V brushless gasoline pump based on phase voltage feedback as described in any one of claims 1 to 7.

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