High integration fan lamp power supply and motor driving method and system

Abstract

This invention proposes a highly integrated fan light power supply and motor driving method and system, belonging to the field of power supply and motor driving technology. It involves rectifying and filtering the filtering and rectifying network, performing high-frequency switching on the power conversion unit, performing secondary voltage reduction on the step-down and isolation module, power-on startup of the main control unit, real-time signal acquisition from the sampling network, performing closed-loop calculation on the pulse modulation unit based on operating condition information and user commands, controlling the gates of the three-phase full-bridge switching transistors through complementary bridge arm control signals, driving the fan motor through sequential alternating large currents, calculating the lighting demand based on the motor's operating status, and controlling the constant current control module and sound circuit through dimming drive and prompt trigger signals to achieve closed-loop interaction. This invention significantly improves the system's integrated stability, anti-interference capability, and response consistency in multimodal interaction under complex operating conditions.

Description

Technical Field

[0001] This invention proposes a highly integrated fan light power supply and motor driving method and system, which relates to the field of power supply and motor driving technology, specifically to the field of highly integrated fan light power supply and motor driving technology. Background Technology

[0002] Traditional fan lights typically separate AC power supply, brushless motor drive, lighting dimming, and voice prompts into multiple independent modules. These modules lack a unified control center and data interaction, resulting in overall system lag and high hardware costs. Furthermore, conventional methods often rely on software control logic with fixed parameters. For example, they fail to consider torque pulsation caused by motor cogging when setting dead zones, or fail to eliminate phase errors caused by analog-to-digital conversion timing misalignment and sampling network filtering delays when acquiring multiple signals. This makes it difficult to balance accuracy and stability in motor speed control, and it's also challenging to achieve absolute synchronization between lighting and feedback triggering. Consequently, these systems struggle to meet the increasingly demanding application requirements of highly integrated fan lights for control safety and response consistency under complex loads and interference. Summary of the Invention

[0003] This invention provides a highly integrated fan light power supply and motor driving method and system to solve the above-mentioned problems: This invention proposes a highly integrated fan-light power supply and motor driving method and system, the method comprising: S1. The filter rectifier network is rectified and filtered by external AC to obtain high voltage DC. The high voltage DC is used to perform high-frequency switching on the power conversion unit to obtain isolated main power supply and primary auxiliary power. The isolated main power supply is used to perform secondary step-down on the step-down and isolation module to obtain lighting drive power and secondary isolation power. S2. Power on the main control unit through the secondary isolation power supply to obtain core computing power. Use the core computing power to collect signals from the sampling network in real time to obtain operating status parameters. Use the operating status parameters in combination with peripherals and rotor feedback to read the operating conditions and user commands. S3. The pulse modulation unit is closed-loop calculated using operating condition information and user instructions to obtain complementary bridge arm control signals. The gate control of the three-phase full-bridge switching transistors is performed using the complementary bridge arm control signals to obtain sequentially alternating large currents. The fan motor is then driven by the sequentially alternating large currents to achieve smooth and efficient rotation. S4. Calculate the lighting demand by pulse width modulation based on the motor's operating status to obtain dimming drive and prompt trigger signals; control the constant current control module and sound circuit with high and low levels using the dimming drive and prompt trigger signals to obtain the set brightness effect and system prompt sound, thus completing the closed-loop interaction.

[0004] Furthermore, the system includes: The conversion step-down module is used to rectify and filter the filter rectifier network through external AC to obtain high voltage DC. The high voltage DC is then used to perform high-frequency switching on the power conversion unit to obtain isolated main power supply and primary auxiliary power. The isolated main power supply is then used to perform secondary step-down on the step-down and isolation module to obtain lighting drive power and secondary isolation power. The data acquisition module is used to power on the main control computing unit through the secondary isolation power supply to obtain core computing capabilities. It then uses these core computing capabilities to acquire real-time signals from the sampling network to obtain operating status parameters. Finally, it combines these operating status parameters with peripheral and rotor feedback to obtain comprehensive readings of operating conditions and user commands. The control and drive module is used to perform closed-loop calculations on the pulse modulation unit based on operating condition information and user commands to obtain complementary bridge arm control signals. The complementary bridge arm control signals are used to control the gates of the three-phase full-bridge switching transistors to obtain sequentially alternating large currents. The sequentially alternating large currents are used to excite and drive the fan motor to achieve smooth and efficient rotation. The calculation and control module is used to perform pulse width modulation calculation on the lighting demand based on the motor's operating status, and obtain dimming drive and prompt trigger signals; it controls the constant current control module and sound circuit with high and low levels through the dimming drive and prompt trigger signals to obtain the set brightness effect and system prompt sound, thus completing the closed-loop interaction.

[0005] The beneficial effects of this invention are as follows: This method integrates high-voltage conversion, low-voltage control, motor drive, intelligent algorithm, lighting dimming, and sound and light feedback into a single control process, which solves the problems of independent operation of each functional module of traditional fan lights, inability to reuse the main control computing power, and fragmented signal links. It realizes integrated high-integration management of the entire process from mains power input to terminal output, improves the overall system control efficiency and collaborative response capability, and greatly reduces the complexity of peripheral circuits and system cost caused by multi-chip collaboration. Attached Figure Description

[0006] Figure 1 This is a schematic diagram of a highly integrated fan-light power supply and motor driving method; Figure 2 Flowchart of multi-level isolated power supply and distribution and step-down conversion; Figure 3 Flowchart of flyback high-frequency coupling and RCD clamping filter control; Figure 4 Flowchart for powering on the core computing unit and acquiring multi-terminal status; Figure 5 This is a flowchart of multi-source signal identification based on RC filtering and Kalman fusion; Figure 6 This is a flowchart of the full-bridge drive and stator excitation commutation control of the motor. Figure 7 This is a flowchart of dynamic compensation for cogging torque based on back EMF sensing. Figure 8 Flowchart for constant current lighting dimming and buzzer trigger feedback; Figure 9 Flowchart for synchronous parallel drive of dual-channel PWM registers; Figure 10 This is a schematic diagram of an AC input rectifier and filter network. Detailed Implementation

[0007] The preferred embodiments of the present invention will be described below with reference to the accompanying drawings. It should be understood that the preferred embodiments described herein are for illustration and explanation only and are not intended to limit the present invention.

[0008] Example 1 One embodiment of the present invention provides a highly integrated fan light power supply and motor driving method, the method comprising: S1. The filter and rectifier network is rectified and filtered by an external AC source to obtain high-voltage DC (e.g., ...). Figure 10 As shown, the power conversion unit is subjected to high-frequency switching via high-voltage DC to obtain isolated main power supply and primary auxiliary power. The main power supply is used to perform secondary step-down on the step-down and isolation module to obtain lighting drive power and secondary isolation power. S2. Power on the main control unit through the secondary isolation power supply to obtain core computing power. Use the core computing power to collect signals from the sampling network in real time to obtain operating status parameters. Use the operating status parameters in combination with peripherals and rotor feedback to read the operating conditions and user commands. S3. The pulse modulation unit is closed-loop calculated using operating condition information and user instructions to obtain complementary bridge arm control signals. The gate control of the three-phase full-bridge switching transistors is performed using the complementary bridge arm control signals to obtain sequentially alternating large currents. The fan motor is then driven by the sequentially alternating large currents to achieve smooth and efficient rotation. S4. Calculate lighting demand using pulse width modulation based on motor operating status to obtain dimming drive and alert trigger signals; control the constant current control module and sound circuit with high and low levels using these signals to obtain the set brightness effect and system alert sound, completing closed-loop interaction. Figure 1 As shown.

[0009] The second-order RC low-pass filter circuit is a passive or low-pass active network composed of two resistors and two capacitors cascaded together. Its frequency cutoff point is determined by the product of the resistor and capacitor values, i.e., the time constant. This time constant is set to be much greater than the main oscillation frequency of the switching power supply, so as to filter out high-frequency switching noise and power grid interference in the sampling link, while being lower than the sampling frequency of the microcontroller's analog-to-digital conversion to ensure that the useful signal is effectively preserved.

[0010] Low ESR smoothing energy storage capacitors refer to energy storage type electrolytic or film capacitors with extremely low equivalent series resistance. These capacitors generate very little internal heat loss during high-frequency charge and discharge cycles, which can significantly reduce the internal temperature rise of the capacitor caused by high-frequency ripple current impact, slow down electrolyte evaporation and physical aging, and ensure high stability of the output dynamic voltage while absorbing large DC ripple.

[0011] Lagrange interpolation is a mathematical fitting algorithm based on polynomial curves. Its function is to extrapolate or interpolate approximately continuous values ​​of the target ideal time by constructing a high-order polynomial function based on the data points before and after the known discrete sampling time. This enables the reconstruction of time-displaced data caused by the polling timing between different channels of the analog-to-digital converter into synchronous data pairs that are absolutely aligned on the time axis.

[0012] Fast recovery switching transistors refer to power semiconductor diodes with extremely short reverse recovery times, typically in the nanosecond range. Their physical characteristic is that when the device switches from forward conduction to reverse turn-off, it can quickly remove and clear the minority carrier stored charge accumulated in the internal PN junction, thereby effectively preventing the phenomenon of high-frequency voltage ringing at the secondary rectifier terminal due to excessive reverse recovery current, which in turn couples to the primary transformer.

[0013] Piezoelectric ceramic sheets are electroacoustic transducers with inverse piezoelectric effect. When the material is subjected to an alternating electric field applied by alternating electrical signals at both ends, its internal lattice structure will produce regular mechanical strain and deformation, thereby causing the diaphragm or vibrating diaphragm attached to its surface to produce corresponding mechanical bending vibration, which in turn pushes the surrounding air to produce audio sound waves that can be perceived by the user.

[0014] The RCD clamping branch is a transient spike absorption network consisting of a fast recovery switching transistor, a snubber capacitor, and a bleeder resistor connected in parallel. At the moment the power switching transistor is turned off, the snubber capacitor quickly captures the high-voltage reverse spike energy released by the leakage inductance of the transformer primary and secondary windings. Then, when the switching transistor is turned on, the overvoltage energy accumulated across the capacitor is dissipated as heat through the parallel bleeder resistor, thereby fundamentally eliminating the risk of voltage breakdown of the rectifier diode caused by commutation ringing overshoot due to leakage inductance.

[0015] The safety dead zone period refers to the extremely short turn-off waiting period artificially inserted between the upper and lower power switching transistors on the same bridge arm in a full-bridge or half-bridge inverter drive circuit during the moment of alternating conduction switching. Its function is to ensure that the lower transistor can only start conducting after the upper transistor is completely turned off, preventing short circuits caused by the physical delay of the charging and discharging of the gate capacitance of the power transistor itself, thereby avoiding physical burnout of the power switching transistor due to instantaneous large current surge.

[0016] The electromagnetic rotating magnetic field is a rotating magnetomotive force generated by the vector synthesis of three single-phase pulsating magnetic fields in the air gap in a time phase sequence after three-phase alternating current is applied to the stator windings distributed at a 120-degree angle in space. The amplitude of this rotating magnetomotive force remains constant within one electrical cycle, while its spatial vector angle continuously moves forward with time, thus forming a composite magnetic field that moves forward continuously at synchronous speed in the inner cavity of the motor stator.

[0017] Cogging torque pulsation refers to the periodic microscopic changes in air gap magnetic resistance caused by the presence of cogging teeth in the stator core when the rotor permanent magnet passes through the cogging position during low-speed operation of a permanent magnet motor. This results in slight fluctuations in electromagnetic torque, which, when transmitted to the mechanical shaft and fan blade load, cause perceptible speed jitter and electromagnetic noise.

[0018] Multi-channel polling scanning refers to the main control micro-operation unit sequentially applying level reading operations to the input ports according to a pre-programmed order under the time base triggered by the system timer interrupt. By inserting tiny time intervals before and after the readings for software debouncing, it confirms one by one whether there is a valid logic level toggling signal at each user interaction interface, thereby avoiding the misjudgment of a single operation as multiple triggers due to mechanical button bounce.

[0019] State machine transition determination refers to the process by which the system's main control program, after receiving and parsing comprehensive operating condition information and user instructions, compares and verifies the legality of the transition between the currently executed task step and the next target step based on the internally preset logical transition condition table. Once the condition is met, the program execution pointer is pointed to the new task module and a new control strategy is started, thereby achieving an orderly, controllable, and safe transition between different working modes of the system.

[0020] Hardware-level asynchronous loading refers to the physical process by which the peripheral bus inside the microcontroller synchronously copies the configuration data in the compare register to the core shadow register bound to the peripheral pin, driven directly by a hardware trigger signal without the active intervention of the central processing unit software instructions. This loading process can be completed within a single clock cycle, thus avoiding microsecond-level timing misalignment that may be caused by software-driven writing at different times.

[0021] Multimodal information transmission refers to the system simultaneously informing external users of the current operating status of the device through two distinct physical perception channels—visual light effect output and auditory audio alarm—on the same time reference after completing the current operation task. This multi-channel parallel feedback mechanism can effectively improve the accuracy of users' judgment of device status and the comprehensiveness of information acquisition under different environmental noise and lighting conditions.

[0022] The input filtering and rectification operation involves connecting the AC mains power to the EMI filter network. Through the differential-mode / common-mode impedance mismatch of the common-mode inductor and safety capacitor, high-frequency conducted interference is physically blocked. Then, the clean AC is sent to the full-bridge rectifier stack. The negative half-cycle of the AC is cut off by the alternating conduction of four diodes, generating a unidirectional pulsating high-voltage DC.

[0023] The flyback switch and isolated power supply operation involves connecting the rectified high-voltage DC to the main flyback controller, which controls the internal high-voltage power transistor to switch on and off at a set fixed frequency using pulse width modulation. When the switch is on, energy is stored in the primary magnetizing inductance of the transformer in the form of magnetic energy. When it is off, the energy is induced through the secondary winding and output to the load through the rectifier diode and the energy storage capacitor. At the same time, an auxiliary flyback circuit is set up to independently generate low-voltage starting power. The power supply circuits of different voltage levels are physically isolated through the isolated DC-DC conversion module.

[0024] The multi-source data acquisition and fusion operation, triggered by a clock interrupt, sequentially starts the analog-to-digital converter to sample the voltage divider and current detection network according to a predetermined cycle. At the same time, it reads the level status of the infrared remote control, buttons, and motor Hall sensors through polling. Considering the physical hysteresis of the sampling channel, after reading the raw data, the system immediately performs phase hysteresis compensation on the voltage and current data preprocessed by the RC network, and calculates the instantaneous speed and spatial angle by combining the leading and trailing edges of the motor rotor Hall pulse. Finally, all state parameters are input into the Kalman filter for weighted fusion, and the comprehensive load information without bias error is output.

[0025] The closed-loop commutation and dead-time adaptive operation, based on the integrated load information and user speed control commands, is performed by the main control unit. When the internal timer generates the commutation moment, it first calls the pre-stored position interference phase deviation table, calculates the commutation deviation caused by the current physical position of the rotor tooth slots by looking up the table, and then converts the deviation into a proportional fine-tuning value of the safe dead-time period. This fine-tuning value is loaded into the gate timing of the bridge arm control signal to ensure that there is a sufficient conduction waiting window at the moment of switching between the upper and lower bridge arms. Then, the drive signal with dynamic dead time is output to the three-phase full-bridge power transistor to realize the sequential excitation of the stator winding by the alternating large current.

[0026] The concurrent audio-visual feedback operation, performed by the main control unit, synchronously queries two independent pulse width modulation (PWM) registers after confirming stable motor operation. One register generates a dimming duty cycle based on the target brightness, driving the constant current control module's enable terminal to rapidly switch and adjust to output a smooth lighting current. The other register generates a buzzer trigger duty cycle based on fault or normal mode, driving the pre-amplifier switch to output a matching frequency alternating electrical signal to excite the buzzer. Both registers are synchronously loaded the instant the timer counter overflows, ensuring complete synchronization between changes in light brightness and audible alarms on a millisecond-level time base.

[0027] The working principle and technical effect of the above technical solution are as follows: This method uses external AC input as the initial energy source, converts the power frequency AC into high-voltage pulsating DC through a filter and rectifier network, and then achieves staged isolation and voltage reduction conversion of AC to isolated DC, high voltage to low voltage, and single-channel to multi-channel energy through the high-frequency switching action of the power conversion unit, forming the main power supply and auxiliary power supply of the system. The secondary-side isolated current wakes up the core main control computing unit, enabling it to obtain the physical basis for executing signal processing. It uses the core computing power to digitally read the system voltage, current, temperature and other sampling networks, and combines the external human-machine interface and motor rotor Hall feedback to extract the real-time load condition of the current system and the user's operation intention, completing the fusion of upper-level logic perception and input information. According to the rotor feedback and operating condition command, the computing unit outputs a complementary bridge arm control signal with dead time to drive the three-phase full-bridge power transistors, inverting DC power into three-phase alternating current that is alternately conducted according to predetermined logic and injecting it into the motor stator to establish a rotating magnetic field to pull the rotor. Based on the feedback of motor operating status and lighting setting requirements, the system independently outputs PWM dimming drive signals and buzzer trigger signals to control the constant current lighting module and sound-generating device respectively, forming the final visual light effect and auditory feedback, completing the complete control link from physical energy acquisition to human-machine interaction closed loop.

[0028] This method integrates high-voltage conversion, low-voltage control, motor drive, intelligent algorithms, lighting dimming, and audio-visual feedback into a single control process. This solves the problems of independent operation of each functional module in traditional fan lights, the inability to reuse the main control computing power, and the fragmentation of signal links. It achieves integrated high-integration management of the entire process from mains power input to terminal output, improves the overall system's control efficiency and collaborative response capability, and greatly reduces the complexity of peripheral circuits and system costs caused by multi-chip collaboration.

[0029] In one embodiment of the present invention, S1 includes: By using external AC mains power to filter out high-frequency noise and suppress spikes in the front-end input filter protection network, a clean AC power after filtering out interference is obtained. A unidirectional pulsating high-voltage direct current is obtained by full-wave rectification and conversion of a bridge rectifier using pure alternating current. By using high-voltage direct current to perform high-frequency switching and transformer coupling transformation on the main power flyback controller, a main power supply that is completely isolated from the primary high voltage is obtained. The auxiliary flyback controller is independently switched and stepped down by high-voltage direct current to obtain low-voltage starting power for the primary control unit. The main power supply performs secondary voltage reduction and smoothing filtering on the step-down constant current unit to obtain the lighting drive power for the subsequent light effect system. The main power supply further steps down the voltage of the isolated DC-DC converter module to obtain the secondary isolated control power for system feedback and communication. Figure 2 As shown.

[0030] The working principle and technical effect of the above technical solution are as follows: This method utilizes the differential-mode and common-mode inductors and safety capacitor network at the input end to form a filter, which performs physical impedance mismatch and bypass absorption on the conducted interference and high-frequency differential-mode noise superimposed in the mains power line, obtaining a pure AC waveform to reduce the burden on the subsequent rectification stage. After the pure AC power enters the full-wave bridge rectifier, the alternating conduction of the four bridge arm diodes flips the upper and lower half cycles of the AC sine wave to the same polarity, forming a unidirectional pulsating high-voltage DC. This high-voltage DC is divided into two main branches: one branch enters the main power flyback controller, which uses a high-frequency switch to cut off the current in the primary coil of the transformer, inducing a voltage physically isolated from the primary side in the secondary winding; the other branch enters the auxiliary flyback controller, which generates a low-voltage start-up current through independent high-frequency isolation step-down, providing the initial operating power for the main control circuit. The main power supply obtained is further divided into two paths as needed: one path is stepped down and smoothed by a step-down constant current unit to generate stable lighting drive power for the light effect components; the other path enters the isolation DC-DC converter module, and is converted by a high-frequency isolation switch to form the secondary isolation control power used for control system communication and feedback, ensuring the safety isolation of the control side and preventing interference from the high-voltage side from being conducted to the low-voltage side.

[0031] This method utilizes a dedicated auxiliary flyback controller to independently generate low-voltage startup power, ensuring that the main control unit maintains priority response for low-voltage logic even when the power stage experiences abnormal overload. This mitigates the risk of sudden power failure and loss of control logic when the main power supply fails. Simultaneously, a dedicated isolated DC-DC converter completely separates the power required for control feedback from the high-voltage energy path. This not only improves the electromagnetic interference immunity of the low-voltage control system and reduces physical interference from higher harmonics to the control signal, but also enables refined physical isolation of power supply networks with different voltage levels and isolation requirements.

[0032] In one embodiment of the present invention, the step of using high-voltage direct current to perform high-frequency switching and transformer coupling transformation on the main power flyback controller to obtain a main power supply completely isolated from the primary high voltage includes: By using high-voltage DC to perform high-frequency pulse width modulation switching on and off on the high-voltage power switch tube built into the main power flyback controller, an excitation alternating current in the primary winding that changes with the duty cycle and rapidly rises to its peak value is obtained. By using an excitation alternating current to establish the magnetic flux corresponding to the ampere-turns of the primary coil coupled to the same magnetic core, the high-frequency alternating magnetic induction intensity inside the magnetic core changes with the current waveform at the same frequency and alternates in direction. By using high-frequency alternating magnetic induction intensity to perform Faraday electromagnetic induction coupling on the secondary winding coil that is close to the physical cross section of the magnetic core and completely insulated from the primary side, a secondary induced electromotive force is obtained across the physical isolation boundary between the primary and secondary sides. The secondary induced electromotive force controls the forward conduction of the rectifier diodes connected in series in the secondary circuit. The RCD clamping branch, which is connected across the diodes and consists of a fast recovery switch and an RC snubber network, absorbs leakage inductance energy and suppresses spikes, thereby obtaining a rectified current that eliminates commutation voltage spikes caused by transformer winding leakage inductance and has a smooth voltage slope. The rectified current cycles the low-ESR smoothing energy storage capacitor connected in parallel to the secondary output terminal, and combined with the frequency response characteristics of the RCD clamping branch, it physically suppresses high-frequency switching ripple, resulting in a main power supply with extremely low dynamic voltage drop and safe isolation. Figure 3 As shown.

[0033] The rectified current is obtained by using an RCD clamping branch, which is connected across the diode and consists of a fast recovery switch and an RC snubber network, to absorb leakage inductance energy and suppress spikes. By applying instantaneous forward conduction drive to the rectifier diode in the secondary circuit through the secondary induced electromotive force, a transient high-frequency oscillating current is obtained in which the PN junction inside the diode switches from reverse cutoff to forward conduction. The clamping capacitor inside the RCD clamping branch connected across the rectifier diode is instantaneously charged by the transient high-frequency oscillating current, so that the potential of the excessively high reverse electromotive force energy released by the leakage inductance of the transformer secondary winding is rapidly accumulated across the clamping capacitor. By rapidly accumulating the potential across the clamping capacitor, the power resistor connected in series inside the RCD clamping branch is converted and dissipated as heat, thus achieving a decaying energy dissipation process that converts the instantaneous high voltage spike generated by the transformer leakage inductance into heat release. By performing reverse discharge feedback on the clamping capacitor through the attenuation energy dissipation process, and combining the fast recovery switch connected in parallel across the rectifier diode to rapidly discharge the parasitic capacitance, the transient high-frequency ringing overshoot caused by the reverse recovery current during commutation is eliminated, and a smooth and physically constrained rectified voltage waveform is formed across the rectifier diode. By injecting low-impedance charging into the low-ESR smoothing energy storage capacitor connected in parallel at the secondary output terminal through the physically constrained rectified voltage waveform, the commutation spikes caused by transformer leakage inductance are eliminated, and premature aging and thermal runaway of the smoothing capacitor caused by high-frequency current impact are suppressed, resulting in a pure and physically limited rectified current output.

[0034] The working principle and technical effect of the above technical solution are as follows: This method is a physical deconstruction of the core power conversion action of the flyback controller. The high-voltage switching transistor inside the controller is turned on and off at high frequency under the control of the drive signal, causing the excitation alternating current in the primary winding to rise and fall rapidly with the duty cycle switching. This current flows through the primary coil, generating ampere-turn flux and establishing a strong alternating magnetic field intensity that varies with time inside the core. According to Faraday's law of electromagnetic induction, this alternating magnetic field passes through the physical cross-section of the secondary winding close to the core, generating a secondary induced electromotive force (EMF) across the primary-secondary isolation boundary. When the secondary induced EMF is in the positive direction, the secondary-side series rectifier diode is turned on. At this time, the RCD clamping branch connected across the diode actively absorbs the high-voltage reverse spike released by the transformer's primary and secondary leakage inductance at the moment of switch turn-off: the clamping capacitor is rapidly charged to intercept the overvoltage energy, and then the parallel power resistor is used for heat dissipation, thereby effectively suppressing the ringing overshoot caused by leakage inductance. After peak clipping, the rectified current flows into a large, smooth energy storage capacitor with low ESR. Combined with the frequency response characteristics of the RCD clamping branch, the residual high-frequency switching ripple is further physically limited and smoothed, ultimately achieving a clean, low-temperature-rise, and voltage-drop-controlled main power supply.

[0035] This method solves the problem of power transistor breakdown and EMI exceeding limits caused by transient voltage spikes due to transformer physical leakage inductance and diode reverse recovery effect during high-frequency operation of flyback converters, without adding extra heat sinks or increasing transformer design margin, without adding extra heat sinks or increasing transformer design margin. Through the synergistic filtering of low ESR smoothing energy storage capacitor and RCD clamping branch frequency characteristics, the voltage ripple amplitude and dynamic drop amplitude at the DC output are significantly reduced, improving the physical stability and power supply quality of the main power supply when dealing with instantaneous large dynamic load jumps.

[0036] In one embodiment of the present invention, S2 includes: The main control microprocessor unit is powered on and its ports are initialized and configured by the secondary isolation control power supply to obtain the core processing capabilities of the system. By configuring the frequency of the internal clock module and triggering timer interrupts through the system's core processing capabilities, a stable system sampling period reference can be obtained. The system's core processing capabilities are used to periodically acquire analog-to-digital conversion signals from the input voltage divider and current detection network to obtain real-time electrical status parameters. The system's core processing capabilities are used to perform multi-path polling scans of the user interaction interface to obtain user operation commands. By combining real-time electrical status parameters with user operation commands and feedback from the motor rotor Hall sensor, the system comprehensively identifies and reads the data to obtain current load condition information and omnidirectional motor position feedback. Figure 4 As shown.

[0037] The working principle and technical effects of the above technical solution are as follows: This method utilizes the secondary-side isolation control current to perform low-level reset and port level state initialization configuration of the micro-computing unit, completing the physical preparation of the internal interrupt vector table, stack pointer, and peripheral clock, thereby obtaining the core processing capability of the system with instruction fetching and execution capability. The core computing unit configures the frequency division and multiplication parameters of the internal clock module, and starts the timer to generate periodic hardware interrupts, providing a unified time reference for subsequent high-precision analog-to-digital conversion and algorithm control. With a stable sampling clock, the computing unit sequentially initiates and reads the analog-to-digital conversion of the input voltage divider network and current detection network according to a pre-set polling cycle, converting analog electrical physical quantities into digital quantities to obtain real-time electrical state parameters for computation. Simultaneously, the computing unit scans and performs hardware debouncing on the directly connected human-machine interface port at a fixed polling interval to obtain user operation commands. The system combines the real-time electrical parameters and user commands with the logically encoded state of the three-phase brushless motor rotor Hall feedback, performing comprehensive mapping and logical association internally to obtain the actual mechanical load condition of the current system and the absolute position of the motor rotor in the spatial coordinate system.

[0038] This method precisely configures and triggers timed interrupts through an internal clock module, changing the traditional approach of relying on software delays or external independent watchdogs for sampling cycles. This effectively improves the jitter resistance and timing determinism of analog-to-digital conversion sampling. By leveraging the system's core computing power to perform parallel multi-channel polling scans of the voltage and current sampling network and the human-machine interface port, a mechanism is achieved to simultaneously acquire electrical status and user interaction intent within a single task cycle. This solves the problem of key information loss or response lag caused by insufficient sampling channels or timing conflicts in low-voltage control systems, significantly improving the system's comprehensive perception capability and real-time response speed to load changes and external environmental changes.

[0039] In one embodiment of the present invention, the step of comprehensively identifying and reading current load condition information and omnidirectional motor position feedback by combining real-time electrical status parameters with user operation commands and feedback from a motor rotor Hall sensor includes: By dynamically comparing and judging the preset safety voltage and current thresholds set inside the system through real-time electrical status parameters, the system obtains the judgment result and the first-level risk warning sign indicating whether the system is currently on the edge of overload or undervoltage. By mapping and matching the internal preset speed adjustment and dimming mode registers through the decoded and extracted user operation commands, the working mode and target action index that the system should execute can be obtained. The phase difference between the leading and trailing edges of the Hall logic state timing is calculated by using the multi-channel phase pulse signals fed back by the motor rotor Hall sensor to obtain real-time physical coordinate parameters that reflect the current instantaneous speed and absolute rotor position angle of the motor. By combining the real-time physical coordinate parameters with the time constant matching and hardware preprocessing of the second-order RC low-pass filter circuit connected to the output of the voltage divider network and the current detection network, and the timing alignment calculation of the fixed phase lag caused by the difference in the analog-to-digital sampling period of each signal, a synchronous multi-source data block that eliminates power frequency interference and high-frequency random noise is obtained. Through the synchronous multi-source data block, the first-layer risk warning sign and the target action index, Kalman filtering weighted fusion calculation is performed in the fault tolerance data area pre-divided by the core computing unit to obtain comprehensive working condition information that eliminates the bias error caused by temperature drift, offset and electromagnetic interference of single-channel sensors and calculates the confidence level exceeding the preset threshold. The integrated operating condition information is used to dynamically trigger and update the state machine of the internal main control loop and determine step jumps, thereby obtaining the underlying closed-loop control authority instructions that adaptively adjust the drive parameters based on the current actual load conditions, such as... Figure 5 As shown.

[0040] Specifically, by combining the real-time physical coordinate parameters with the time constant matching and hardware preprocessing of the second-order RC low-pass filter circuit connected to the output of the voltage divider network and the current detection network, and by performing time alignment calculations on the fixed phase lag caused by the difference in the analog-to-digital sampling period of each signal, a synchronous multi-source data block that eliminates power frequency interference and high-frequency random noise is obtained, including: By using second-order RC low-pass filter circuits at the outputs of the voltage divider network and the current sensing network, the noise signals originating from high-voltage switch ripple and high-frequency transient interference are processed by impedance matching and frequency cutoff based on a specific resistor-capacitor time constant. This process yields original analog voltage and current signals with physical hysteresis characteristics, which have had high-frequency spikes initially filtered out and reduced to the range of analog voltages acceptable to the microcontroller. By alternately polling and sampling the input channels of the multi-channel analog-to-digital converter inside the microcontroller using the original analog voltage and current signals, the fixed phase deviation of the multi-channel converter caused by the conversion waiting time and the physical delay of the hardware RC filter is obtained. By using a multi-channel fixed phase deviation, the high-speed clock cycles inside the microcontroller are counted and the completion interruption time of each analog-to-digital conversion channel is recorded, thereby obtaining the physical sampling relative lag timestamp of each signal on the time scale. By using the relative lag timestamps of the physical sampling of each signal, data rearrangement and delay compensation are performed in the circular buffer of the microcontroller's on-chip random access memory to obtain a strictly synchronized multi-source raw data group that has eliminated RC physical delay and ADC sampling timing differences on the time scale. By synchronizing multiple source raw data groups and combining Lagrange interpolation calculations between voltage and current physical quantities, a synchronized multi-source data block that is fully phase-aligned and can truly reflect the same transient operating condition is obtained.

[0041] The working principle and technical effects of the above technical solution are as follows: This method unfolds the underlying mathematical and physical aspects of multi-source sensor signal fusion and intelligent decision-making. The system first dynamically compares the collected real-time electrical state parameters with internally fixed safety voltage and current thresholds. Once an out-of-bounds violation is detected, a first-level risk warning is immediately output. Simultaneously, the decoded user remote control command is matched with a preset speed control and dimming register mapping table to obtain a clear execution target index. At this point, the multi-channel phase pulse signals fed back by the Hall sensor are calculated using the phase difference between the leading and trailing edges to determine the instantaneous physical coordinate parameters of the motor. Due to external power grid noise, physical delays in the sampling circuit, and polling time differences between analog-to-digital converter channels, the system combines these physical coordinate parameters with the time constant of a second-order RC low-pass filter circuit connected to the output of the sampling network. A time-domain alignment algorithm is used to eliminate the fixed phase lag caused by RC delays and different ADC trigger times in each signal, thus removing power frequency interference and obtaining synchronous multi-source data blocks. This data block is combined with early warning flags and target indexes, and a Kalman filter-weighted fusion model is deployed within a pre-defined fault-tolerant data area in the core storage unit. Through iterative calculations of prediction-observation-update, the cumulative errors caused by sensor temperature drift and electromagnetic interference are eliminated. Finally, this high-confidence operating condition information is used to dynamically trigger state transitions in the internal state machine, granting the system the adaptive adjustment capability to cope with real load changes.

[0042] This method addresses the issues of microscopic data asynchrony and phase distortion caused by conversion time differences and external interference in traditional synchronous sampling of multi-source heterogeneous signals (analog voltage, current, and digital Hall pulses) by pre-applying a second-order RC low-pass filter circuit at the sampling network output and performing timing alignment calculations based on phase lag during the algorithm phase. Simultaneously, by establishing a Kalman filter weighted fusion model with a fault tolerance range within the core computing unit, it effectively overcomes the problem of false triggering of erroneous amplitude limiting protection caused by temperature drift and electromagnetic interference from a single sensor. This enables high-confidence condition determination of the system under complex electromagnetic environments, significantly improving the system's fault tolerance and precise control performance under power grid fluctuations and load abrupt changes.

[0043] In one embodiment of the present invention, S3 includes: By combining the omnidirectional motor position feedback with the user-defined rotation speed command, the internal pulse width modulation generator is compared with the benchmark and the closed-loop control algorithm is calculated to obtain a complementary bridge arm drive control signal with a safe dead zone cycle. The gate drive front-end circuit is converted and amplified by the bridge arm drive control signal to obtain a gate control signal with sufficient drive capability. By using gate control signals to alternately turn the three-phase full-bridge power switching transistors on and off, a three-phase alternating drive current is obtained by alternating output according to a predetermined commutation logic. By sequentially energizing the stator coils of the fan motor with a three-phase alternating drive current, an electromagnetic rotating magnetic field that advances sequentially according to phase is obtained. By using an electromagnetic rotating magnetic field to pull and drive the rotor permanent magnet, a smooth and efficient uniform rotation operation of the fan motor is achieved. Figure 6 As shown.

[0044] The working principle and technical effect of the above technical solution are as follows: Based on the omnidirectional position feedback and the target speed set by the user, this method performs internal comparison of set values ​​and closed-loop control calculations such as PID control to generate a bridge arm drive control signal with complementary phase and a safe dead-zone cycle. This low-voltage drive signal is then enhanced by the gate drive pre-stage circuit, and through level shifting and power amplification conversion, obtains a gate control signal sufficient to overcome the input capacitance and physical threshold of the MOS transistor. This control signal is applied to the three-phase full-bridge inverter circuit composed of 6 power switching transistors, which alternately controls the conduction and cutoff of the upper and lower bridge arms according to the motor commutation logic, converting DC bus power into three-phase alternating drive current. This alternating current flows into the three-phase stator windings of the motor, and using the principle of the force on a current-carrying conductor in a magnetic field, it gradually excites the rotor according to the current position phase, synthesizing an electromagnetic rotating magnetic field that changes progressively with phase angle in space. The electromagnetic rotating magnetic field applies magnetic pull to the pre-magnetized permanent magnets of the rotor, driving the motor to drive the fan blade load to run smoothly, efficiently and at a constant speed.

[0045] This method fundamentally solves the risk of high-to-low side shoot-through short circuits caused by physical conduction delay during the switching of upper and lower bridge arms in three-phase full-bridge switching transistors by introducing complementary bridge arm control signals with a safe dead-time period. Through level conversion and power amplification of the gate drive pre-stage circuit, it ensures that the weak chip PWM logic signal can effectively drive the gate capacitor of the high-power MOSFET, solving the signal isolation and insufficient drive problems between the weak current control domain and the strong current power domain. By calculating the three-phase alternating current according to the commutation logic using a closed-loop control algorithm, the commutation timing accuracy and motor operating efficiency of the fan motor under different load conditions are effectively improved.

[0046] In one embodiment of the present invention, the step of sequentially energizing the stator coils of a fan motor with a three-phase alternating drive current to obtain an electromagnetic rotating magnetic field that progresses sequentially in phase includes: By alternately outputting three-phase alternating drive current according to a predetermined commutation logic, the coils of different phase bands of the three-phase star-connected stator winding are sequentially injected with fixed phase intervals to obtain a single-phase magnetic field that is periodically and alternately established in spatial order between the stator slots of the motor. By using the electromagnetic superposition effect of the periodic alternation of each single-phase magnetic field on the time axis, the spatial vector of the composite magnetic field between the stator and rotor air gap is calculated by vector superposition, and a composite electromagnetic field with an approximately constant vector amplitude and uniform rotation in the phase sequence direction is obtained within a complete electric cycle. By synthesizing an electromagnetic field to conduct electromagnetic traction on the pre-fabricated N / S pole magnetic field on the rotor permanent magnet through like pole repulsion and unlike pole attraction, a tangential electromagnetic torque that always exists along the direction of motor rotation is obtained. By injecting energy and accelerating the rotational inertia of the rotor and its connected fan blades through tangential electromagnetic torque, a dynamic speed increase or decrease process that meets the target speed regulation command is obtained. By using the reverse-phase induced electromotive force generated in the stator winding during the dynamic rotation speed process, the charging and discharging phase shift of the RC absorption network connected in parallel between the three-phase output terminal of the motor and ground is sensed and calculated to obtain the position interference phase deviation value that reflects the linkage between the physical structure of the rotor cog and the stator winding. The safe dead zone period parameter of the complementary bridge arm control signal output by the internal pulse width modulation generator is dynamically and proportionally adjusted by the position interference phase deviation value. Combined with the absorption characteristics of the RC absorption network, the commutation instantaneous lead or lag conduction compensation is performed to obtain the corrected drive current that eliminates the periodic torque pulsation caused by the cogging effect. By injecting the modified drive current into the stator coils, high-efficiency rotational operation is achieved that suppresses back EMF overshoot while offsetting torque fluctuations, enabling smooth and jitter-free operation under any load disturbance. Figure 7 As shown.

[0047] Specifically, the charging and discharging phase shift of the RC absorption network connected in parallel between the three-phase output terminals of the motor and ground is sensed and calculated using the reverse-phase induced electromotive force generated in the stator windings during the dynamic rotational speed process. This yields a position interference phase deviation value reflecting the linkage between the rotor cogging physical structure and the stator windings, including: By using the reverse-phase induced electromotive force generated by the stator winding cutting the rotor permanent magnet during dynamic speed, the series capacitors inside the RC absorption network connected in parallel between the three-phase output terminals of the motor and ground are charged and discharged in opposite polarities. This results in the microscopic charging and discharging phase shift phenomenon generated in the RC network at the moment when the back electromotive force waveform crosses zero when the rotor passes through a tooth position. The voltage drop slope across the series capacitor in the RC absorption network is sampled and sensed at high frequency by using the micro-charging and discharging phase shift phenomenon to obtain the non-uniform position interference phase angle that reflects the change in the spatial position of the rotor cogging magnetic field and the stator winding linkage. The reference deviation of the target drive signal output by the pulse width modulation generator inside the microcontroller is calculated by using the non-uniform position interference phase angle to obtain the position interference phase deviation value of the electrical torque lagging or leading when the rotor permanent magnet passes through the physical slit of the stator slot and the commutation switch tube operates. By using the position interference phase deviation value to perform low-rate dynamic lookup and proportional fine-tuning of the dead time parameter table for generating complementary bridge arm control signals, the corrected safe dead time period parameter is obtained, which adaptively adjusts the conduction time of the upper and lower bridge arms according to the degree of physical interference of the tooth groove. By combining the corrected safety dead zone cycle parameters with the discharge delay characteristics of the RC absorption network, bidirectional compensation is performed at the moment of commutation. This results in a corrected drive current output that suppresses the torque fluctuations that would otherwise occur at the hardware level through the RC absorption network and achieves jitter-free operation.

[0048] The working principle and technical effect of the above technical solution are as follows: The driving current is injected into different phase coils of the three-phase star-connected stator according to a predetermined commutation logic, generating single-phase magnetic fields that are periodically and alternately established in spatial order within the stator's inner wall slots. These single-phase magnetic fields appear in sequence along the time axis, and according to the principle of magnetic field superposition, they are vector-superimposed in the air gap to form a composite electromagnetic field with constant amplitude and uniform rotation. This composite electromagnetic field links with the N / S magnetic field on the rotor poles, forming a tangential torque that drives the rotor's rotation through the electromagnetic principle of like poles repelling and unlike poles attracting. However, during rotor operation, due to the physical geometric interference between the stator slots and the permanent magnet poles, inherent cogging torque pulsations occur, causing slight speed fluctuations. Therefore, the system extracts the reverse-phase induced electromotive force generated by the stator windings cutting the rotor magnetic lines of force during dynamic speed operation, measures the charging and discharging phase shift of the RC absorption network connected in parallel between the motor's three-phase output terminals and ground, and thus calculates the position interference phase deviation caused by the linkage of the slot physical structure. By utilizing this deviation, the system dynamically fine-tunes the safety dead-time period parameter of the complementary bridge arm signal output by the PWM modulator, and uses the discharge delay characteristics of the RC absorption network itself to perform lead or lag conduction compensation at the moment of commutation, thereby eliminating the effect of periodic torque pulsation.

[0049] This method abandons the traditional fixed dead-time commutation strategy and creatively utilizes the reverse-phase induced electromotive force generated during the dynamic speed process of the motor to sense the charging and discharging phase displacement of the RC absorption network connected in parallel at the motor phase line terminals in real time. This mechanism solves the problems of mechanical torque fluctuation and electromagnetic noise caused by the deviation between the commutation phase angle and the physical position of the rotor under the influence of cogging effect in traditional fan-light drives. By converting the position interference phase deviation into a dynamic proportional adjustment of the safe dead-time parameter of the bridge arm control signal, the mechanical vibration and electromagnetic howling caused by the cogging positioning torque of the fan blades at low speeds are reduced, significantly improving the quietness and smoothness of the fan-light operation under any load.

[0050] In one embodiment of the present invention, S4 includes: Based on the stable operating state of the motor and the specific requirements of the external lighting settings, the duty cycle of the pulse width modulation output is dynamically allocated and calculated to obtain the lighting switch signal and the prompt tone trigger signal with adjustable duty cycle. The constant current control drive module enable terminal is controlled by the lighting switch signal to perform high-frequency on / off regulation, so as to obtain a smooth lighting current that meets the set brightness requirements. The lighting current is used to power and excite the light effect components, so as to obtain the light effect output with the brightness level required by the user and without flicker. The high and low level switching of the pre-switch of the sound driving circuit is controlled by the prompt tone trigger signal to obtain the electrical signals emitted in the switching sequence. The system generates sound by driving a sound generator with an electrical signal to produce different alert sounds for normal operation and abnormal fault states, thus completing a full information reporting and closed-loop interactive feedback mechanism. Figure 8 As shown.

[0051] The working principle and technical effect of the above solution are as follows: The lighting switch signal is connected to the enable pin of the constant current control drive module. Through high-frequency on / off regulation, the output current is kept smooth within the target value range, avoiding light flicker caused by sudden current changes. The smooth lighting current enters the light-emitting component, exciting the recombination of electrons and holes in the semiconductor light-emitting lattice to produce a constant light effect that meets the brightness setting requirements. Simultaneously, the prompt tone trigger signal controls the pre-switching transistor of the sound-generating drive circuit, causing it to generate an alternating electrical signal that switches between high and low frequencies at a specific frequency. This electrical signal drives the piezoelectric ceramic plate inside the piezoelectric sound generator to produce mechanical bending vibration, thereby pushing air to emit a status prompt tone indicating normal system operation or fault alarm. Finally, the system reports and provides feedback to the user through a combination of light effect and sound.

[0052] This method integrates the previously independent lighting adjustment and status reporting actions into a unified execution feedback response by synchronizing the duty cycle allocation calculation of the lighting dimming signal and the buzzer prompt trigger signal. On the one hand, the high-frequency on / off adjustment of the constant current control drive module's enable terminal solves the problem of perceptible low-frequency flicker that easily occurs in traditional linear dimming or low-frequency PWM dimming. On the other hand, through internal synchronous calculation, it ensures that when the motor state changes or the user presses a button, the change in light effect and the sound feedback are triggered synchronously without physical time delay, improving the user's intuitive experience of the system's consistent response.

[0053] In one embodiment of the present invention, the step of dynamically calculating the duty cycle allocation of the pulse width modulation output device based on the stable operating state of the motor and specific external requirements for lighting settings, to obtain a lighting switch signal and a prompt tone trigger signal with adjustable duty cycle, includes: Based on the motor's operating status and the specific brightness level requirements set by the external lighting effect, the duty cycle of the two independent pulse width modulation registers inside the main control unit is configured and calculated in parallel to obtain the light effect control variable and the prompt tone control variable that are strictly synchronized in time reference but change independently in duty cycle value. By adjusting the power switch enable terminal of the constant current control drive module at a high frequency microsecond level pulse width duty cycle through the light effect control variable, the lighting power supply current whose drive current amplitude changes linearly and smoothly with the duty cycle is obtained. By using the lighting power supply current to DC excite the light-emitting component, a continuous luminous flux output that meets the user-defined brightness threshold is obtained, which is generated by stimulated emission of the semiconductor light-emitting lattice. By applying a high-frequency on / off level switch to the base of the pre-drive transistor of the sound driving circuit through the prompt tone control variable, an electrical signal excitation source that alternates according to the driving frequency is obtained. The piezoelectric ceramic sheet or electromagnetic diaphragm inside the sound generator is mechanically vibrated by an electrical signal excitation source to obtain a function confirmation prompt tone when the system is operating normally or a specific frequency alarm tone when the system is in a fault alarm state. By combining light flux with alarm tones of specific frequencies in a temporal sequence, multimodal information is conveyed to the user, completing the system's full closed-loop interactive feedback and status reporting. Figure 9 As shown.

[0054] Specifically, based on the motor's operating status and the specific brightness level requirements set externally for lighting effects, the duty cycle of the two independent pulse width modulation registers within the main control unit is configured in parallel. This yields lighting effect control variables and prompt tone control variables that are strictly synchronized in time but change independently in duty cycle value, including: By counting up to the preset period overflow value through the central counter register of the same general-purpose timer in the main control unit, the hardware-level asynchronous loading action is triggered simultaneously for the two comparison registers internally mapped to the two independent PWM outputs, so as to obtain the parallel comparison data loading event that is absolutely aligned on the same microsecond phase of the central clock counter. By comparing data loading events in parallel, two comparison registers are driven to write the independently calculated light effect duty cycle value and the prompt tone duty cycle value into their respective core memory units at the beginning of the same clock cycle, thereby obtaining a synchronous register configuration word that eliminates any relative time base drift in the time dimension. By synchronously registering the configuration word, the high-frequency level flipping control is performed on the comparison result between the corresponding pulse width modulation output pin level states and the central counter to obtain the light effect control variable and the prompt tone control variable, which have significant differences in duty cycle values ​​but whose waveform phase edge start points are strictly coincident. By adjusting the duty cycle of the power switch enable pin of the constant current drive module at a high frequency microsecond level through the light effect control variable, a smooth lighting power supply current that is absolutely aligned with the user's visual signal at the moment of lighting is turned on is obtained. At the same time, by applying an electrical signal that alternates at a specific alarm frequency to the pre-control terminal of the piezoelectric driver of the sound driving circuit through the prompt tone control variable, a piezoelectric excitation signal that is absolutely synchronized with the lighting signal at the moment the sound command is issued is obtained.

[0055] The working principle and technical effect of the above technical solution are as follows: After obtaining the motor operating status and lighting setting requirements, this method directly sends an instruction to the central counting register of the same general-purpose timer inside the main control unit. At the instant when the central counting register counts up and reaches the preset period overflow value, a hardware-level loading pulse is simultaneously sent to two independent comparison registers mapped to two independent PWM outputs, causing the two comparison registers to simultaneously write the light effect duty cycle data and the prompt tone duty cycle data into their core storage units at the beginning of the same clock cycle. Since the loading actions of both are in the same internal bus clock phase, relative time base drift is completely eliminated in the time dimension, resulting in synchronous register configuration words with completely overlapping phases. These two synchronous register configuration words control the level of the two hardware output pins to flip during the high-frequency counting cycle, generating two PWM waveforms with different duty cycles but whose rising and falling edges absolutely overlap. The lighting control variable with adjustable duty cycle is connected to the enable pin of the constant current drive module, generating a smooth lighting power supply current at the instant the user presses the button; at the same time, the prompt tone control variable is connected to the sound drive pre-control terminal, emitting a strictly synchronous piezoelectric excitation signal.

[0056] This method utilizes the overflow event of the central counter register of the same general-purpose timer to drive two independent PWM registers to perform absolute parallel loading at the low-level bus level, solving the microsecond-level duty cycle assignment delay problem caused by the step-by-step writing of registers in ordinary software. This mechanism effectively eliminates the acoustic-optical phase drift and pulse distortion caused by inconsistent register configuration timing in dual-channel synchronous output scenarios, significantly improving the absolute synchronization accuracy of acoustic-optical feedback in multimodal human-machine interaction. This low-level register-level parallel configuration greatly reduces the design difficulty of complex software mutexes and delay compensation logic required in embedded software development to avoid timing races.

[0057] According to one embodiment of the present invention, the system includes: The conversion step-down module is used to rectify and filter the filter rectifier network through external AC to obtain high voltage DC. The high voltage DC is then used to perform high-frequency switching on the power conversion unit to obtain isolated main power supply and primary auxiliary power. The isolated main power supply is then used to perform secondary step-down on the step-down and isolation module to obtain lighting drive power and secondary isolation power. The data acquisition module is used to power on the main control computing unit through the secondary isolation power supply to obtain core computing capabilities. It then uses these core computing capabilities to acquire real-time signals from the sampling network to obtain operating status parameters. Finally, it combines these operating status parameters with peripheral and rotor feedback to obtain comprehensive readings of operating conditions and user commands. The control and drive module is used to perform closed-loop calculations on the pulse modulation unit based on operating condition information and user commands to obtain complementary bridge arm control signals. The complementary bridge arm control signals are used to control the gates of the three-phase full-bridge switching transistors to obtain sequentially alternating large currents. The sequentially alternating large currents are used to excite and drive the fan motor to achieve smooth and efficient rotation. The calculation and control module is used to perform pulse width modulation calculation on the lighting demand based on the motor's operating status, and obtain dimming drive and prompt trigger signals; it controls the constant current control module and sound circuit with high and low levels through the dimming drive and prompt trigger signals to obtain the set brightness effect and system prompt sound, thus completing the closed-loop interaction.

[0058] The working principle and technical effects of the above technical solution are as follows: This system uses external AC input as the initial energy source. Through a filtering and rectifier network, the power frequency AC is converted into high-voltage pulsating DC. Then, through the high-frequency switching action of the power conversion unit, the energy is converted from AC to isolated DC, from high voltage to low voltage, and from single-channel to multi-channel in a phased isolation and step-down manner, forming the system's main power supply and auxiliary power supply. The secondary-side isolated current wakes up the core main control and computing unit, providing it with the physical basis for signal processing. Utilizing its core computing capabilities, it digitally reads the system's voltage, current, and temperature sampling networks. Combined with the external human-machine interface and motor rotor Hall feedback, it extracts the current system's real-time load condition and user operation intent, completing the fusion of upper-level logic perception and input information. Based on rotor feedback and operating condition commands, the computing unit outputs a complementary bridge arm control signal with dead time to drive the three-phase full-bridge power transistors, inverting DC power into three-phase alternating current that is alternately conducted according to predetermined logic and injecting it into the motor stator to establish a rotating magnetic field that pulls the rotor. Based on the feedback of motor operating status and lighting setting requirements, the system independently outputs PWM dimming drive signals and buzzer trigger signals to control the constant current lighting module and sound-generating device respectively, forming the final visual light effect and auditory feedback, completing the complete control link from physical energy acquisition to human-machine interaction closed loop.

[0059] This system integrates high-voltage power conversion, low-voltage power control, motor drive, intelligent algorithms, lighting dimming, and audio-visual feedback into a single control process. This solves the problems of independent operation of each functional module in traditional fan lights, the inability to reuse the main control computing power, and the fragmentation of signal links. It achieves integrated high-level management of the entire process from mains power input to terminal output, improves the overall system's control efficiency and collaborative response capability, and greatly reduces the complexity of peripheral circuits and system costs caused by multi-chip collaboration.

[0060] Example 2 This embodiment further optimizes the calculation method for the safe dead zone period.

[0061] The method includes steps S1-S5.

[0062] S1. The external AC filter network is rectified and filtered, and the power conversion unit performs high-frequency switching conversion. The power is then converted into lighting drive power and secondary isolation power through the step-down and isolation module, providing the power supply foundation for the subsequent main control unit and motor drive.

[0063] S2. The main control micro-computing unit is started through secondary isolation to periodically collect feedback from the voltage divider network, current detection network and motor rotor Hall sensor, and to perform timing alignment and fusion processing on different collected signals to obtain current load condition information, power supply status and all-round motor position feedback.

[0064] S3. Based on the omnidirectional motor position feedback and the user-set rotation speed command, a complementary bridge arm control signal with a safe dead zone period is generated through the internal pulse width modulation generator. This signal controls the three-phase full-bridge power switching transistors to alternately turn on and off, so that the three-phase alternating drive current is injected into the stator coil of the fan motor according to the predetermined commutation logic, driving the rotor permanent magnet to rotate.

[0065] S4. During the dynamic operation of the fan motor, the reverse-phase induced electromotive force generated by the stator winding and the phase change of charging and discharging of the RC absorption network are detected. Combined with the current commutation reference time and the feedback from the motor rotor Hall sensor, the position interference phase deviation value, which characterizes the degree of lead or lag of the current actual commutation time relative to the target commutation time, is obtained.

[0066] S5. Based on the position interference phase deviation value obtained in step S4, the operating condition coupling correction is further performed on the safe dead zone cycle in Example 1 by combining the current motor electric angular velocity, the degree of change of driving current and the degree of deviation of power supply voltage, to obtain the target safe dead zone cycle parameter corresponding to the current control cycle, and the target safe dead zone cycle parameter is loaded into the internal pulse width modulation generator to control the three-phase full-bridge power switching transistors in the next commutation cycle.

[0067] S5 includes S51-S53.

[0068] S51. Determine the load coupling phase compensation time corresponding to the current operating condition based on the current position interference phase deviation value, motor electric angular velocity and the degree of change in drive current.

[0069] Specifically, the main control micro-computing unit reads the position interference phase deviation value obtained in step S4, and simultaneously reads the current electric angular velocity of the motor determined by the feedback from the motor rotor Hall sensor.

[0070] First, based on the current position interference phase deviation value and the current motor electrical angular velocity, the position interference phase deviation, represented by electrical angles, is converted into the corresponding commutation time offset at the current operating speed. The higher the motor electrical angular velocity, the smaller the actual time offset corresponding to the same position interference phase deviation; the lower the motor electrical angular velocity, the larger the actual time offset corresponding to the same position interference phase deviation. This avoids the problem in Example 1 where different speed states use the same time compensation amplitude when directly adjusting according to a fixed ratio based on the position interference phase deviation.

[0071] Furthermore, the main control microprocessor unit reads the drive current obtained by the current detection network in the current control cycle and the previous control cycle, and compares the degree of change of drive current in adjacent control cycles.

[0072] When the change in drive current between adjacent control cycles is small, it indicates that the current load of the fan motor is in a relatively stable state. At this time, the commutation time offset is mainly determined based on the position interference phase deviation and the motor's electric angular velocity.

[0073] When the drive current changes more in adjacent control cycles, it indicates that the fan motor is in a state of load change, acceleration, deceleration, or blade resistance change. Then, the correction degree of the aforementioned commutation time offset is further increased or decreased according to the degree of drive current change, so that the final compensation time simultaneously reflects rotor cogging position interference, current operating speed, and actual load changes.

[0074] The load coupling phase compensation time is thus obtained.

[0075] The position interference phase deviation retains the leading or lagging directional attribute. Therefore, the load coupling phase compensation time also retains the corresponding compensation direction, which is used to determine whether the subsequent safety dead zone period should be increased or decreased relative to the basic safety dead zone period.

[0076] Through the above processing, the method of directly determining the periodic change of the safe dead zone by the position interference phase deviation in Example 1 is further transformed into first determining the offset on the time scale based on the current operating speed, and then using the actual drive current change to perform load coupling correction on the time offset.

[0077] S52. Determine the switch safety constraint coefficient corresponding to the current operating condition based on the current position interference phase deviation value, motor electric angular velocity, and current power supply voltage deviation.

[0078] Specifically, the main control micro-computing unit continues to use the position interference phase deviation value and motor electric angular velocity in step S51, and reads the current power supply voltage obtained from the voltage divider network from the synchronous multi-source data formed in step S2. The current power supply voltage is compared with the predetermined reference power supply voltage to determine the degree of deviation of the current power supply voltage relative to the normal operating state.

[0079] The switch safety constraint coefficient is used to evaluate the extent to which the load coupling phase compensation time obtained in step S51 can actually affect the safety dead zone period.

[0080] When the position interference phase deviation is within the normal range, the motor running speed is within the stable range, and the current supply voltage is close to the reference supply voltage, it indicates that the current position feedback and power switch commutation conditions have high stability, and a small restriction is imposed on the load coupling phase compensation time obtained in step S51.

[0081] When the position interference phase deviation increases significantly, it indicates that the current commutation moment deviates significantly from the target commutation position; when the motor is at low speed, the identification stability of the reverse induced electromotive force and the charging and discharging phase of the RC absorption network decreases; when the current supply voltage deviates significantly from the reference supply voltage, it indicates that the current commutation electrical conditions of the three-phase full-bridge power switch deviate from the normal operating state.

[0082] When one or more of the above situations occur, the degree of switch safety constraint is increased so that the load coupling phase compensation time obtained in step S51 cannot be directly applied to the basic safety dead zone cycle, so as to avoid excessive transient adjustment of the safety dead zone cycle due to single position interference phase abnormality, low speed identification error or power supply status change.

[0083] Therefore, steps S51 and S52 both use the position interference phase deviation value and the motor electric angular velocity as correlation parameters, but they introduce different operating state parameters respectively.

[0084] In step S51, the degree of change in drive current is further introduced to determine the degree of commutation compensation that actually needs to be implemented under the current operating conditions; in step S52, the degree of supply voltage deviation is further introduced to determine the degree to which the current operating conditions of the power switch allow the actual effect of the commutation compensation.

[0085] As a result, load changes and power supply status no longer form independent judgment results, but instead form compensation requirements and safety constraints respectively around the same safety dead zone cycle.

[0086] S53. Based on the load coupling phase compensation time obtained in step S51 and the switch safety constraint coefficient obtained in step S52, the basic safety dead zone period is fused and corrected to obtain the target safety dead zone period parameter.

[0087] Specifically, the basic safe dead zone period, the minimum allowable safe dead zone period, and the maximum allowable safe dead zone period are preset in the main control micro-computing unit.

[0088] The basic safety dead zone period is the reference value of the safety dead zone period used when the three-phase full-bridge power switch is in normal operating condition in Example 1; the minimum safety dead zone period is used to ensure that there is a necessary turn-off waiting time between the upper and lower power switches in the same bridge arm; the maximum safety dead zone period is used to avoid excessive shortening of the effective conduction time due to excessively long dead zone time.

[0089] The main control microprocessor unit first determines the direction and degree of adjustment of the basic safety dead zone cycle based on the load coupling phase compensation time obtained in step S51, and then limits the degree of adjustment based on the switch safety constraint coefficient obtained in step S52.

[0090] When the fan motor load is relatively stable, the position interference phase identification is reliable, and the power supply voltage is within the normal range, the restriction on the load coupling phase compensation time is reduced, so that it can be fully applied to the basic safety dead zone cycle, thereby completing the commutation compensation for the current position interference state.

[0091] When the power supply voltage deviates significantly, the motor is at low speed, or the current position interference phase deviation increases abnormally, the limitation on the load coupling phase compensation time is increased, so that the actual correction amount of the final load to the basic safety dead zone cycle is reduced, thereby avoiding the dead zone parameter from changing significantly with the result of a single abnormal detection.

[0092] After completing the above fusion correction, the obtained safe dead zone period is compared with the allowable minimum safe dead zone period and the allowable maximum safe dead zone period. When the obtained safe dead zone period is lower than the allowable minimum safe dead zone period, the allowable minimum safe dead zone period is adopted; when the obtained safe dead zone period is higher than the allowable maximum safe dead zone period, the allowable maximum safe dead zone period is adopted; when the obtained safe dead zone period is between the two, the fusion-corrected safe dead zone period is directly adopted, thereby obtaining the target safe dead zone period parameter corresponding to the current control cycle.

[0093] The main control microprocessor unit writes the target safety dead time cycle parameter into the dead time parameter area corresponding to the internal pulse width modulation generator, and completes the update before the start of the next commutation cycle. It then controls the three-phase full-bridge power switching transistors to alternately turn on and off according to the corrected dead time through the gate drive front-end circuit.

[0094] Furthermore, to avoid frequent jumps in the safety dead zone period caused by transient interference, the target safety dead zone period parameter can be updated when the interference phase deviation at the current position maintains the same direction of change for multiple consecutive control cycles, or when the drive current change reaches the preset change condition for multiple consecutive control cycles. For isolated position interference phase anomalies that only occur in a single control cycle, the target safety dead zone period parameter of the previous control cycle is continued to be used.

[0095] The above processing can be completed using the existing main control micro-computing unit, motor rotor Hall sensor feedback, current detection network, voltage divider network and RC absorption network in Example 1, without the need to add new detection components or change the connection relationship of the three-phase full-bridge power switching transistors.

[0096] The working principle and technical effects of the above technical solution are as follows: To further address the issue that the actual commutation compensation requirements differ for the same position interference phase deviation under different speeds, loads, and power supply conditions.

[0097] Specifically, this embodiment first uses the current position interference phase deviation and the motor electrical angular velocity to determine the commutation offset on the time scale, and then uses the degree of change in drive current to perform load coupling correction on the commutation offset to obtain the load coupling phase compensation time that reflects the current actual compensation requirements; further, using the same position interference phase deviation and motor electrical angular velocity, and combined with the degree of supply voltage deviation, a switch safety constraint coefficient is formed to evaluate the degree to which the compensation is allowed to be actually loaded to the safe dead zone period under the current operating conditions; finally, the load coupling phase compensation time is correlated with the switch safety constraint coefficient, and the target safe dead zone period parameter is determined within the allowable maximum and minimum safe dead zone period range.

[0098] Therefore, in this embodiment, the degree of change in drive current is used to characterize "how much compensation is needed under the current operating condition", and the degree of deviation in power supply voltage is used to characterize "how much compensation is allowed under the current operating condition". The two form a parameter correlation through common position interference phase deviation and motor electric angular velocity, and ultimately work together to affect the target safety dead zone period.

[0099] By adopting the above method, the safety dead zone control method, which mainly relies on proportional adjustment based on position interference phase deviation, is further optimized into a condition-coupled safety dead zone control method that simultaneously considers rotor position interference, running speed, load changes, and power supply status. This reduces the possibility of insufficient or excessive commutation compensation during fan motor acceleration and deceleration, sudden load changes, and power supply voltage fluctuations, and maintains the necessary safety commutation margin for the three-phase full-bridge power switching transistors while suppressing cogging torque pulsation.

[0100] Obviously, those skilled in the art can make various modifications and variations to this invention without departing from its spirit and scope. Therefore, if these modifications and variations fall within the scope of the claims of this invention and their equivalents, this invention also intends to include these modifications and variations.

Claims

1. A highly integrated fan-light power supply and motor driving method, characterized in that, The method includes: S1. The filter rectifier network is rectified and filtered by external AC to obtain high voltage DC. The high voltage DC is used to perform high-frequency switching on the power conversion unit to obtain isolated main power supply and primary auxiliary power. The isolated main power supply is used to perform secondary step-down on the step-down and isolation module to obtain lighting drive power and secondary isolation power. S2. Power on the main control unit through the secondary isolation power supply to obtain core computing power. Use the core computing power to collect signals from the sampling network in real time to obtain operating status parameters. Use the operating status parameters in combination with peripherals and rotor feedback to read the operating conditions and user commands. S3. The pulse modulation unit is closed-loop calculated using operating condition information and user instructions to obtain complementary bridge arm control signals. The gate control of the three-phase full-bridge switching transistors is performed using the complementary bridge arm control signals to obtain sequentially alternating large currents. The fan motor is then driven by the sequentially alternating large currents to achieve smooth and efficient rotation. S4. Calculate the lighting demand by pulse width modulation based on the motor's operating status to obtain dimming drive and prompt trigger signals; control the constant current control module and sound circuit with high and low levels using the dimming drive and prompt trigger signals to obtain the set brightness effect and system prompt sound, thus completing the closed-loop interaction.

2. The highly integrated fan light power supply and motor driving method according to claim 1, characterized in that, S1 includes: By using external AC mains power to filter out high-frequency noise and suppress spikes in the front-end input filter protection network, clean AC power is obtained. A unidirectional pulsating high-voltage direct current is obtained by full-wave rectification and conversion of a bridge rectifier using pure alternating current. The main power supply is obtained by using high-voltage direct current to perform high-frequency switching and transformer coupling transformation on the main power flyback controller; Low-voltage starting power is obtained by independently switching and stepping down the auxiliary flyback controller using high-voltage direct current. The main power supply is used to perform secondary voltage reduction and smoothing filtering on the step-down constant current unit to obtain the lighting drive power; The main power supply is used to further step down the voltage of the isolated DC-DC converter module to obtain the secondary-side isolated control power.

3. The highly integrated fan light power supply and motor driving method according to claim 2, characterized in that, The process of obtaining main power supply by high-frequency switching and transformer coupling transformation of the main power flyback controller using high-voltage direct current includes: High-frequency pulse width modulation is used to switch the high-voltage power switching transistor built into the main power flyback controller on and off using high-voltage direct current to obtain excitation alternating current. The high-frequency alternating magnetic induction intensity is obtained by establishing the magnetic flux corresponding to the ampere-turns of the primary coil coupled on the same magnetic core using an excitation alternating current. A secondary induced electromotive force is obtained by using high-frequency alternating magnetic induction intensity to perform Faraday electromagnetic induction coupling on the secondary winding coil that is close to the physical cross section of the magnetic core and completely insulated from the primary side. The secondary induced electromotive force is used to control the forward conduction of the rectifier diode connected in series in the secondary circuit. The leakage inductance energy is absorbed and the spike is suppressed by the RCD clamping branch connected across the diode and composed of a fast recovery switch and an RC snubber network, so as to obtain the rectified current. The rectified current cycles the low-ESR smoothing energy storage capacitor connected in parallel to the secondary output terminal for charge and discharge. Combined with the frequency response characteristics of the RCD clamping branch, the high-frequency switching ripple is physically suppressed to obtain the main power supply.

4. The highly integrated fan light power supply and motor driving method according to claim 1, characterized in that, S2 includes: The main control microprocessor unit is powered on and its ports are initialized and configured by the secondary isolation control power supply to obtain the core processing capabilities of the system. The system's core processing capabilities are used to configure the frequency of the internal clock module and trigger timer interrupts to obtain the system sampling period reference. The system's core processing capabilities are used to periodically acquire analog-to-digital conversion signals from the input voltage divider and current detection network to obtain real-time electrical status parameters. The system's core processing capabilities are used to perform multi-path polling scans of the user interaction interface to obtain user operation commands. By combining real-time electrical status parameters with user operation commands and feedback from the motor rotor Hall sensor, the current load condition information and all-around motor position feedback are obtained.

5. The highly integrated fan light power supply and motor driving method according to claim 4, characterized in that, The process involves comprehensively identifying and reading real-time electrical status parameters and user operation commands combined with feedback from the motor rotor Hall sensor to obtain current load condition information and omnidirectional motor position feedback, including: By dynamically comparing and judging the preset safety voltage and current thresholds set inside the system through real-time electrical status parameters, the judgment result and the first-level risk warning sign are obtained. By mapping and matching the internal preset speed adjustment and dimming mode registers through the decoded and extracted user operation commands, the working mode and target action index are obtained. The phase difference between the leading and trailing edges of the Hall logic state timing is calculated by using the multi-channel phase pulse signal fed back by the Hall sensor of the motor rotor to obtain the real-time physical coordinate parameters. By combining the real-time physical coordinate parameters with the time constant matching and hardware preprocessing of the second-order RC low-pass filter circuit connected to the output of the voltage divider network and the current detection network, and by performing time alignment calculation on the fixed phase lag of each signal caused by the difference in analog-to-digital sampling period, synchronous multi-source data blocks are obtained. Using the synchronous multi-source data blocks, the first-layer risk warning flags, and the target action index, Kalman filtering weighted fusion calculations are performed within the fault tolerance data area pre-divided by the core computing unit to obtain comprehensive operating condition information. The state machine of the internal main control loop is dynamically triggered, updated, and step jumps are determined by the comprehensive operating condition information to obtain the underlying closed-loop control authority instructions.

6. The highly integrated fan light power supply and motor driving method according to claim 1, characterized in that, S3 includes: By combining the omnidirectional motor position feedback with the user-defined rotation speed command, the internal pulse width modulation generator performs benchmark comparison and closed-loop control algorithm calculation to obtain the bridge arm drive control signal. The gate control signal is obtained by converting the signal level and amplifying the power of the gate drive front-end circuit through the bridge arm drive control signal. The three-phase full-bridge power switching transistors are alternately turned on and off by the gate control signal to obtain the three-phase alternating drive current. An electromagnetic rotating magnetic field is obtained by sequentially energizing the stator coils of the fan motor with a three-phase alternating drive current. The rotor permanent magnet is pulled and driven by an electromagnetic rotating magnetic field to achieve uniform rotation.

7. The highly integrated fan light power supply and motor driving method according to claim 6, characterized in that, The step of sequentially energizing the stator coils of the fan motor with a three-phase alternating drive current to obtain an electromagnetic rotating magnetic field includes: By alternately outputting three-phase alternating drive current according to a predetermined commutation logic, the coils of different phase bands of the three-phase star-connected stator winding are sequentially injected with fixed phase intervals to obtain a single-phase magnetic field. By utilizing the electromagnetic superposition effect of the periodic alternation of various single-phase magnetic fields on the time axis, the spatial vector of the composite magnetic field between the stator and rotor air gap is calculated by vector superposition to obtain the composite electromagnetic field. By synthesizing an electromagnetic field, the N / S pole magnetic field prefabricated on the rotor permanent magnet is subjected to electromagnetic traction through the repulsion of like poles and the attraction of unlike poles, thus obtaining tangential electromagnetic torque. By injecting energy and accelerating the rotational inertia of the rotor and its connected fan blades through tangential electromagnetic torque, a dynamic speed increase or decrease process can be obtained. By using the reverse-phase induced electromotive force generated in the stator winding during the dynamic rotation process, the charging and discharging phase shift of the RC absorption network connected in parallel between the three-phase output terminal of the motor and ground is sensed and calculated to obtain the position interference phase deviation value. The safe dead zone period parameter of the complementary bridge arm control signal output by the internal pulse width modulation generator is dynamically and proportionally adjusted by the position interference phase deviation value, and the RC absorption network is used to compensate for the instantaneous lead or lag conduction during commutation to obtain the corrected drive current. By injecting the modified drive current into the stator coil, high-efficiency rotational operation is achieved.

8. The highly integrated fan light power supply and motor driving method according to claim 1, characterized in that, S4 includes: Based on the stable operating status of the motor and the specific requirements of the external lighting settings, the duty cycle of the pulse width modulation output device is dynamically allocated to obtain the lighting switch signal and the prompt tone trigger signal. The lighting current is obtained by using the lighting switch signal to perform high-frequency on / off regulation control on the enable terminal of the constant current control drive module; The light effect components are powered and energized by the lighting current to obtain light effect output; The high and low level switching control of the pre-switch of the sound driving circuit is controlled by the prompt tone trigger signal to obtain an electrical signal; The sound generator is driven by an electrical signal to vibrate and produce sound, thereby obtaining different prompts and completing the entire information reporting and closed-loop interactive feedback.

9. The highly integrated fan light power supply and motor driving method according to claim 8, characterized in that, The process involves dynamically calculating the duty cycle allocation of the pulse width modulation output device based on the stable operating state of the motor and specific external requirements for lighting settings, to obtain the lighting switch signal and the prompt tone trigger signal, including: Based on the motor's operating status and the specific brightness level requirements set by the external lighting effect, the duty cycle of the two independent pulse width modulation registers inside the main control unit is configured and calculated in parallel to obtain the lighting effect control variables and the prompt sound control variables. The lighting power supply current is obtained by adjusting the high-frequency microsecond-level pulse width duty cycle of the power switch enable terminal of the constant current control drive module through the light effect control variable. By using the lighting power supply current to DC excite the light-emitting components, continuous luminous flux output can be obtained; By applying a high-frequency on / off level switch to the base of the pre-drive transistor of the sound driving circuit through the prompt tone control variable, an electrical signal excitation source is obtained. The piezoelectric ceramic sheet or electromagnetic diaphragm inside the sound generator is mechanically vibrated by an electrical signal excitation source to obtain a function confirmation prompt tone or a specific frequency alarm tone. By combining light flux with alarm sounds of specific frequencies in an orderly manner over time, the system conveys multimodal information to users, completing a full closed-loop interactive feedback and status reporting.

10. A highly integrated fan-light power supply and motor drive system, characterized in that, The system includes: The conversion step-down module is used to rectify and filter the filter rectifier network through external AC to obtain high voltage DC. The high voltage DC is then used to perform high-frequency switching on the power conversion unit to obtain isolated main power supply and primary auxiliary power. The isolated main power supply is then used to perform secondary step-down on the step-down and isolation module to obtain lighting drive power and secondary isolation power. The data acquisition module is used to power on the main control computing unit through the secondary isolation power supply to obtain core computing capabilities. It then uses these core computing capabilities to acquire real-time signals from the sampling network to obtain operating status parameters. Finally, it combines these operating status parameters with peripheral and rotor feedback to obtain comprehensive readings of operating conditions and user commands. The control and drive module is used to perform closed-loop calculations on the pulse modulation unit based on operating condition information and user commands to obtain complementary bridge arm control signals. The complementary bridge arm control signals are used to control the gates of the three-phase full-bridge switching transistors to obtain sequentially alternating large currents. The sequentially alternating large currents are used to excite and drive the fan motor to achieve smooth and efficient rotation. The calculation and control module is used to perform pulse width modulation calculation on the lighting demand based on the motor's operating status, and obtain dimming drive and prompt trigger signals; it controls the constant current control module and sound circuit with high and low levels through the dimming drive and prompt trigger signals to obtain the set brightness effect and system prompt sound, thus completing the closed-loop interaction.

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