An adaptive power supply scheduling method and system for a passive vibration sensing node

Abstract

The application discloses a kind of self-adapting power supply scheduling method and system of passive vibration sensing node, belong to electric power supply and energy management technical field, including obtaining the alternating current generated based on vibration of piezoelectric transducer, after rectification, front-stage energy storage capacitor is introduced to accumulate charge and generate front-stage voltage signal;The signal is impedance matched and voltage transformed, energy transfer current is generated and injected into rear-stage supercapacitor storage, and supercapacitor voltage signal is obtained;After hysteresis comparison and hardware interlock logic processing, power supply switching signal is generated, and supercapacitor power supply is preferentially scheduled accordingly, and when energy is insufficient, it is automatically switched to backup battery to supply power for passive vibration sensing node.The application uses the power supply decision mechanism of hysteresis comparison and hardware interlock logic, combines piezoelectric vibration energy collection and multi-stage energy storage architecture, and can realize intelligent priority scheduling and stable switching of passive vibration sensing node power supply.

Description

Technical Field

[0001] This invention relates to the field of power supply and energy management technology, and in particular to an adaptive power supply scheduling method and system for a passive vibration sensing node. Background Technology

[0002] Passive vibration sensing nodes, as an important component of wireless sensor networks, are widely used in industrial equipment, such as industrial water pumps, for condition monitoring and fault early warning. These nodes are typically deployed in environments where wiring or battery replacement is difficult, making the long-term autonomous operation of their power supply system crucial. Energy harvesting technology, particularly extracting energy from equipment vibration, provides a feasible approach to achieving passive or long-life operation of these nodes, and the design of related power supply and distribution systems is one of the core technologies in this field.

[0003] In related technologies, Chinese invention patent CN109980766B discloses a power management circuit for a vibration energy harvester with hysteresis self-locking function, comprising: a rectifier circuit, an energy storage capacitor, a hysteresis self-locking circuit, an electronic switch, and a voltage regulator circuit. The rectifier circuit is connected to the energy storage capacitor, the energy storage capacitor is connected to the hysteresis self-locking circuit, the hysteresis self-locking circuit is connected to the electronic switch, the electronic switch is connected to the voltage regulator circuit, and the voltage regulator circuit is connected to the application circuit.

[0004] However, the existing technical solutions mentioned above have the following technical defects: The existing solutions do not establish a priority scheduling strategy for environmental vibration energy, fail to maximize the utilization of environmental vibration energy collected by piezoelectric sensors, and rely excessively on backup battery power, resulting in insufficient energy self-sufficiency of the passive vibration sensing nodes, making it difficult to meet the needs of long-term autonomous operation in industrial scenarios. The power switching logic of the existing solutions lacks hardware interlocking and dead-time control mechanisms, failing to guarantee absolute mutual exclusion conduction between the main energy storage and backup batteries during switching, potentially leading to a shoot-through short circuit risk where both power supplies conduct simultaneously, resulting in power supply conflicts, system damage, or operational interruptions. The existing solutions do not utilize the low equivalent series resistance characteristics of supercapacitors for dynamic compensation of the power supply bus. When the RF transmission module of the passive vibration sensing node generates instantaneous high-current consumption pulses, the resulting voltage drop cannot be suppressed, leading to large fluctuations in the power supply bus and affecting the reliability of node data acquisition and communication. Summary of the Invention

[0005] To address the aforementioned issues, this invention provides an adaptive power supply scheduling method and system for passive vibration sensing nodes. Employing a power supply decision mechanism based on hysteresis comparison and hardware interlocking logic, combined with piezoelectric vibration energy harvesting and a multi-level energy storage architecture, it enables intelligent priority scheduling and stable switching of the power supply for passive vibration sensing nodes.

[0006] The above objectives can be achieved through the following approach:

[0007] An adaptive power supply scheduling method and system for a passive vibration sensing node includes: acquiring AC power generated by a piezoelectric transducer based on vibration, rectifying it, and then introducing it into a pre-stage energy storage capacitor to accumulate charge and generate a pre-stage voltage signal; performing impedance matching and voltage transformation on the signal to generate an energy transfer current and injecting it into a subsequent supercapacitor for storage, thus obtaining a supercapacitor voltage signal; generating a power supply switching signal through hysteresis comparison and hardware interlock logic processing, and prioritizing the supercapacitor power supply accordingly, automatically switching to a backup battery to replenish power to the passive vibration sensing node when energy is insufficient.

[0008] Optionally, generating the pre-stage voltage signal includes: receiving the original AC signal output by the piezoelectric transducer and performing full-wave rectification to generate a pulsating DC signal; converging the pulsating DC signal to the plates of the pre-stage energy storage capacitor to continuously and slowly accumulate weak charges to generate an initial accumulated charge; monitoring the potential difference formed across the pre-stage energy storage capacitor by the initial accumulated charge to generate the pre-stage voltage signal.

[0009] Optionally, generating the energy transfer current includes: acquiring the preceding voltage signal and performing voltage threshold detection to generate a preceding activation trigger signal; responding to the preceding activation trigger signal, controlling the switching converter to perform high-frequency chopping processing to generate a high-frequency pulse current; smoothing and filtering the high-frequency pulse current, and adaptively matching and electrically isolating the energy input impedance and the output load impedance to generate the energy transfer current.

[0010] Optionally, generating the supercapacitor voltage signal includes: acquiring the energy transfer current and performing unidirectional conduction control to generate a unidirectional injection current; guiding the unidirectional injection current into the subsequent supercapacitor for large-capacity energy buffer storage to generate dynamic energy storage capacity; and converting the dynamic energy storage capacity into the real-time potential state across the subsequent supercapacitor to generate a supercapacitor voltage signal.

[0011] Optionally, generating the voltage state determination signal includes: comparing the supercapacitor voltage signal with the upper limit threshold of the hysteresis comparator to generate a charge saturation state signal; comparing the supercapacitor voltage signal with the lower limit threshold of the hysteresis comparator to generate a power depletion warning signal; and combining the charge saturation state signal and the power depletion warning signal to perform state maintenance and flipping control to generate the voltage state determination signal.

[0012] Optionally, generating the power supply switching control signal includes: inputting the voltage state determination signal into a hardware interlock module for level mutual exclusion processing to generate a first driving level and a second driving level; applying the first driving level to the control terminal of the first switch connected to the downstream supercapacitor, correspondingly controlling the first switch to be turned on or off, forming a supercapacitor power supply path in a conducting or off state; applying the second driving level to the control terminal of the second switch connected to the backup battery, correspondingly controlling the second switch to be turned on or off, forming a backup battery power supply path in a conducting or off state; ensuring that the first switch and the second switch do not conduct simultaneously through hardware interlock logic, and generating a power supply switching control signal for priority power supply scheduling by combining the on / off states of the supercapacitor and the backup battery.

[0013] Optionally, the step of inputting the voltage state determination signal into the hardware interlock module for level mutual exclusion processing to generate the first drive level and the second drive level includes: extracting the rising edge characteristics and falling edge characteristics of the voltage state determination signal to generate corresponding edge trigger pulses; inputting the edge trigger pulses into the dead time generation circuit for delay blocking processing to generate a dead time isolation signal for staggering the on / off timing of the switching transistors; and performing superposition mutual exclusion logic operations on the dead time isolation signal and the voltage state determination signal to generate the first drive level and the second drive level.

[0014] Optionally, the step of prioritizing the downstream supercapacitor to power the passive vibration sensing node according to the power supply switching control signal, and switching to the backup battery to supplement power supply when the supercapacitor energy is insufficient, includes: responding to the power supply switching control signal, by default turning on the first switch and turning off the second switch, so that the downstream supercapacitor prioritizes powering the passive vibration sensing node; when the supercapacitor voltage signal drops to the lower threshold of the hysteresis comparator, it is determined that the energy storage is insufficient, the first switch is turned off and the second switch is turned on, and the backup battery is switched to power the sensing node; when the supercapacitor voltage signal rises back to the upper threshold of the hysteresis comparator, it is determined that the energy storage is sufficient, the first switch is turned on again and the second switch is turned off, restoring the supercapacitor priority power supply mode.

[0015] Optionally, after generating the power supply switching control signal for priority power supply scheduling, the method further includes: acquiring the stable power supply bus voltage formed under the action of the power supply switching control signal; using the low equivalent series resistance characteristics of the downstream supercapacitor to suppress the voltage drop caused by instantaneous large current; and performing dynamic smoothing compensation on the power supply bus voltage to control the bus voltage fluctuation within the power supply requirement threshold, thereby generating a highly stable and smooth power supply voltage.

[0016] Based on the same inventive concept, this invention also provides an adaptive power supply scheduling system for a passive vibration sensing node. The system includes: an energy acquisition and rectification module for acquiring the raw AC signal generated by the piezoelectric transducer based on the vibration of an industrial water pump, rectifying the raw AC signal, and then introducing it into a pre-stage energy storage capacitor for charge accumulation to generate a pre-stage voltage signal; an impedance matching and transformation module for performing impedance matching and voltage transformation on the pre-stage voltage signal to generate an energy transfer current; a supercapacitor voltage signal generation module for guiding the energy transfer current into a subsequent supercapacitor for energy storage to generate a supercapacitor voltage signal; a hysteresis comparison module for performing hysteresis comparison processing on the supercapacitor voltage signal to generate a voltage state determination signal; and a power supply switching execution module for receiving the voltage state determination signal and executing hardware interlock logic processing to generate a power supply switching control signal. Based on the power supply switching control signal, the subsequent supercapacitor is prioritized to supply power to the passive vibration sensing node, and when the supercapacitor's energy is insufficient, a backup battery is switched to supplement the power supply.

[0017] Compared with the prior art, the present invention has the following advantages:

[0018] This invention improves the system's energy self-sufficiency by prioritizing the collection and distribution of energy for power supply and utilizing environmental vibration energy.

[0019] This invention ensures absolute safety and seamless connection during the switching process between primary and backup power supplies through hardware interlocking and dead-time control logic, thereby reducing the risk of power supply conflicts.

[0020] This invention utilizes supercapacitors to dynamically compensate the power supply bus, suppressing voltage drops caused by instantaneous high current loads and ensuring the stability of the power supply voltage.

[0021] Other features and advantages of the invention will be set forth in the description which follows, and will be apparent in part from the description, or may be learned by practicing the invention. The objects and other advantages of the invention may be realized and obtained by means of the structures pointed out in the description, claims and drawings. Attached Figure Description

[0022] To more clearly illustrate the technical solutions in the embodiments of the present invention or the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0023] Figure 1 This is a flowchart illustrating an adaptive power supply scheduling method for a passive vibration sensing node according to an embodiment of the present invention.

[0024] Figure 2 This is a diagram showing the characteristics of charge accumulation and voltage generation in the preceding stage according to an embodiment of the present invention.

[0025] Figure 3 This is a waveform diagram of high-frequency chopping and energy transfer smoothing according to an embodiment of the present invention.

[0026] Figure 4 This is a smoothing compensation diagram of transient high current pulse and bus voltage in an embodiment of the present invention.

[0027] Figure 5 This is a schematic diagram of the structure of an adaptive power supply scheduling system for a passive vibration sensing node according to an embodiment of the present invention. Detailed Implementation

[0028] To make the objectives, technical solutions, and advantages of the embodiments of the present invention clearer, the technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of the present invention, not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0029] Reference Figure 1 One embodiment of the present invention proposes an adaptive power supply scheduling method for passive vibration sensing nodes. This method employs a power supply decision mechanism based on hysteresis comparison and hardware interlocking logic, combined with piezoelectric vibration energy harvesting and a multi-level energy storage architecture. This enables intelligent priority scheduling and stable switching of the power supply for passive vibration sensing nodes.

[0030] The method described in this embodiment specifically includes:

[0031] S1. Obtain the original AC signal generated by the piezoelectric transducer based on the vibration of the industrial water pump, and after rectifying the original AC signal, import it into the front-stage energy storage capacitor for charge accumulation to generate the front-stage voltage signal.

[0032] Optionally, the generation of the pre-stage voltage signal includes:

[0033] It receives the raw AC signal output from the piezoelectric transducer and performs full-wave rectification to generate a pulsating DC signal.

[0034] The pulsating DC signal is focused onto the plates of the front-stage energy storage capacitor to continuously and slowly accumulate a weak charge, generating an initial accumulated charge.

[0035] The potential difference formed across the front-stage energy storage capacitor by the initial accumulated charge is monitored to generate a front-stage voltage signal.

[0036] Specifically, the characteristics of charge accumulation and voltage generation in the preceding stage are shown in the figure below. Figure 2 As shown, the raw AC signal output from the piezoelectric transducer undergoes a preliminary energy conversion. This raw AC signal typically manifests as a weak AC current with unstable voltage amplitude, synchronized with the vibration frequency of an industrial water pump, requiring processing through a full-wave rectifier bridge. Full-wave rectification is a crucial power conversion method. It utilizes the unidirectional conduction characteristic of diodes to flip the negative half-cycle level of the AC signal to a positive level, thereby converting bidirectional AC into a unidirectional pulsating DC signal. This signal is characterized by a consistently positive voltage direction, but its amplitude fluctuates dramatically with the intensity of the original vibration. This approach aims to capture the energy of each cycle of the AC signal, theoretically doubling the energy conversion efficiency compared to half-wave rectification.

[0037] To smooth out this violently fluctuating pulsating DC signal and collect its weak charge, the system directs it to a pre-stage energy storage capacitor for accumulation. This capacitor acts as a miniature energy storage buffer, with a capacitance value... Typically designed between 10 microfarads and 100 microfarads to balance charging speed and filtering effect. When a pulsating DC signal flows through, the charge it carries accumulates continuously and slowly on the two plates of the capacitor, forming an initial accumulated charge that increases over time. This process transforms discontinuous energy pulses into continuous charge storage.

[0038] To convert the stored physical charge into electrical parameters that can be used for logical judgments in subsequent circuits, the system uses a monitoring circuit to sample the potential difference across the front-stage energy storage capacitor in real time. The magnitude of this potential difference directly reflects the amount of initial accumulated charge and is used to generate the front-stage voltage signal. The generation of this signal follows the fundamental physical laws of capacitance, and its mathematical relationship can be expressed as:

[0039] ,

[0040] in, The generated preceding voltage signal is a voltage value that can be directly measured in the circuit; This represents the initial accumulated charge on the preceding energy storage capacitor, which is obtained by integrating the "pulsating DC signal" over time. This is the capacitance value of the pre-amplifier energy storage capacitor, a known hardware parameter determined during the circuit design phase. The pre-amplifier voltage signal is a DC voltage that slowly rises from zero; when it reaches the activation threshold of the subsequent energy transfer circuit, it triggers the next energy dispatch operation.

[0041] For example, in the field verification of industrial water pump operation status monitoring, a power supply test system for a passive vibration sensing node was built. A piezoelectric transducer was placed in close contact with the surface of the industrial water pump bearing housing to capture the mechanical vibration caused by the pump's rotation and convert it into a raw AC signal. This raw AC signal was input to a full-wave rectifier bridge composed of four diodes, where it was received and rectified. Utilizing the unidirectional conduction characteristic of the diodes, the negative half-cycle level of the AC signal was flipped to a positive level, generating a pulsating DC signal whose voltage direction is always positive but whose amplitude fluctuates violently with vibration. This pulsating DC signal was then focused onto the plates of a pre-stage energy storage capacitor for a continuous and slow accumulation of weak charge. The capacitance value of this pre-stage energy storage capacitor was set as a hardware parameter in the hardware selection. At the end of a specific charging phase, a defined initial accumulated charge is generated on the capacitor plates. Subsequently, the monitoring circuit monitors and samples the potential difference formed across the front-stage energy storage capacitor by the initial accumulated charge in real time. Based on the mathematical and physical relationship formula defined in the instruction manual, the specific calculation process is as follows: Thus, the amplitude is accurately generated. The preceding voltage signal, which is a continuously rising DC voltage signal, will subsequently be compared with the start-up voltage threshold to trigger the next energy dispatch operation.

[0042] S2. Perform impedance matching and voltage transformation on the preceding voltage signal to generate energy transfer current;

[0043] Optionally, the generation of energy transfer current includes:

[0044] The preceding voltage signal is acquired and a voltage threshold is detected to generate a preceding activation trigger signal;

[0045] In response to the pre-stage activation trigger signal, the switching converter is controlled to perform high-frequency chopping processing to generate a high-frequency pulse current.

[0046] The high-frequency pulse current is smoothed and filtered, and the impedance of the energy input terminal and the load impedance of the output terminal are adaptively matched and electrically isolated to generate an energy transfer current.

[0047] Specifically, the waveform diagrams of high-frequency chopping and energy transfer smoothing are as follows: Figure 3 As shown, this is achieved through a dedicated energy conversion and control circuit, the core of which is to realize efficient power transfer from a low-voltage source to a high-voltage load. This process first involves a voltage monitoring unit monitoring the voltage signal from the preceding stage. Continuous data acquisition is performed and compared with a preset start-up voltage threshold. A comparison is made. This threshold is typically set at a low level, such as 0.8 volts to 1.5 volts, to ensure that the front-end energy storage capacitor has accumulated the minimum energy sufficient to start the conversion circuit and sustain its short-term operation. Once detected... Greater than or equal to The input pin of the voltage comparator or microcontroller will immediately output a high-level logic signal, namely the pre-stage activation trigger signal, to wake up and start the subsequent switching converter.

[0048] In response to the activation trigger signal from the preceding stage, the dormant switching converter begins high-frequency chopping. High-frequency chopping is the core operating mechanism of a DC-DC boost converter. It controls a switching transistor to rapidly turn on and off at extremely high frequencies, typically between 100 kHz and 2 MHz. During the on-phase switching, current from the preceding capacitor flows through the inductor, converting electrical energy into stored magnetic energy. During the off-phase switching, the magnetic field energy in the inductor is released, inducing an electromotive force much higher than the input voltage, thus generating a discontinuous high-frequency pulse current. This process is a crucial step in boosting low-voltage DC power to higher voltage levels.

[0049] To make this high-frequency pulsed current suitable for charging supercapacitors, it must be shaped and optimized. First, the pulsed current is rectified by diodes and smoothed by the output capacitor, transforming it into a relatively stable DC current in both direction and amplitude. During this process, the converter control system performs the crucial adaptive matching function, namely Maximum Power Point Tracking (MPPT). It dynamically adjusts the duty cycle or operating frequency of the switching transistors to change the converter's input impedance, making it as close as possible to the energy harvesting source—the internal resistance of the piezoelectric transducer and the preceding capacitor—thereby extracting energy from weak vibrations with maximum efficiency. Simultaneously, if the converter uses a flyback topology, its internal transformer provides electrical isolation, completely separating the input and output terminals, enhancing the system's anti-interference capability and safety. The stable DC output current generated after this series of processes is the final energy transfer current. Its size is determined by energy conversion efficiency and power balance:

[0050] ,

[0051] in, For the generated energy transfer current; The energy conversion efficiency of a switching converter is a coefficient between 0 and 1, determined by the circuit design and the operating point. It is the maximum input power drawn from the preceding circuitry and optimized by the "adaptive matching" algorithm; It is the real-time voltage across the supercapacitor at that time, which is monitored in real time as a dynamically changing load voltage.

[0052] For example, in the verification of the conversion circuit for monitoring the operating status of industrial water pumps, the system first uses a voltage monitoring unit to analyze the voltage signal generated in the previous step. Continuous data acquisition and voltage threshold detection are performed. In the test case, a preset start-up voltage threshold is used. Set as The front-end voltage signal acquired at this time for Because of the detection Greater than The voltage comparator immediately outputs a high-level logic signal, successfully generating the pre-stage activation trigger signal. In response to this pre-stage activation trigger signal, the dormant switching converter is awakened and begins high-frequency chopping processing, controlling the internal switching transistors to... The system rapidly switches on and off at high frequencies, converting the electrical energy in the preceding capacitor into magnetic energy and then releasing it, generating a discontinuous high-frequency pulse current. Subsequently, this high-frequency pulse current is rectified by a diode and smoothed by the output capacitor. The control system then executes a maximum power point tracking (MPPT) algorithm to dynamically adjust the duty cycle of the switching transistors to adaptively match and electrically isolate the energy input impedance from the output load impedance, thereby generating a stable energy transfer current. At the steady-state operating point of this adaptive matching, the maximum input power obtained by the algorithm optimization is... for The real-time voltage across the supercapacitor at that time was obtained through real-time monitoring. for Furthermore, the energy conversion efficiency of this switching converter... The measured value is 0.85. Based on the mathematical formula relating power balance and energy conversion efficiency, the specific calculation process is as follows: Ultimately, through precise calculations and physical transformations, a smooth image of size [size missing] was generated. Energy transfer current It is used for unidirectional injection and energy storage into subsequent supercapacitors.

[0053] S3. Guide the energy transfer current to be injected into the subsequent supercapacitor for energy storage, and generate a supercapacitor voltage signal;

[0054] Optionally, generating the supercapacitor voltage signal includes:

[0055] The energy transfer current is acquired and unidirectional conduction control is performed to generate a unidirectional injection current;

[0056] The unidirectional injected current is guided into the subsequent supercapacitor for large-capacity energy buffer storage, generating dynamic energy storage capacity.

[0057] The dynamic energy storage capacity is converted into the real-time potential state across the supercapacitor, generating a supercapacitor voltage signal.

[0058] Specifically, the process begins with precise control of the path and direction of the energy transfer current. Once the system acquires the energy transfer current, it immediately implements unidirectional conduction control. In engineering, this control is achieved by connecting a Schottky diode with low forward voltage drop in series. This diode ensures that current can only flow from the energy conversion circuit to the energy storage unit, strictly preventing energy leakage from the energy storage unit in the reverse direction, thus generating a strictly unidirectional injection current.

[0059] This unidirectional injection current is stably guided to the electrodes of the subsequent supercapacitor for large-capacity energy buffering and storage. The subsequent supercapacitor is an energy storage element with extremely high capacitance. Typically designed in the range of 0.1 farads to several farads, far exceeding the capacity of the preceding capacitor, it can store enough energy to drive the entire sensing node to complete multiple data acquisition and transmission tasks. When a unidirectional injection current is continuously injected, charge accumulates on the electrode double layer of the supercapacitor, forming a dynamically increasing stored energy quantity over time. This process transforms discrete energy packets into a continuous, centralized energy pool.

[0060] To convert the physically stored charge into an electrical signal that can be recognized and processed by subsequent power supply scheduling logic, the system needs to convert the dynamically stored energy into a potential state in real time. This conversion is based on the fundamental physical principle of capacitors, namely that the voltage across a capacitor is proportional to the amount of charge it stores. By directly measuring the potential difference across the subsequent supercapacitor, the system generates the supercapacitor voltage signal. This signal is a smoothly varying DC voltage, the value of which precisely represents the state of charge of the main energy storage unit. Its mathematical relationship can be expressed as:

[0061] ,

[0062] in, This is the generated supercapacitor voltage signal, which is the direct input for subsequent voltage comparison and power supply switching decisions; The dynamic energy storage capacity accumulated on the subsequent supercapacitor is obtained by integrating the unidirectional injection current over time. This is the nominal capacitance value of the subsequent supercapacitor, a core hardware parameter determined during circuit design. The supercapacitor voltage signal provides the most critical decision-making basis for the entire adaptive power supply scheduling strategy.

[0063] For example, in the verification of the main energy storage charging and discharging characteristics of the passive vibration sensing node, the system first acquires the energy transfer current generated in the previous step and introduces this current into a unidirectional control circuit for unidirectional conduction control. By connecting a Schottky diode with low forward voltage drop characteristics in series in the path, reverse leakage of energy from the energy storage unit is strictly prevented, thereby stably generating a strictly unidirectional unidirectional injection current. Next, this unidirectional injection current is guided into the electrodes of the subsequent supercapacitor for large-capacity energy buffer storage. The nominal capacitance value of this subsequent supercapacitor is selected in the hardware design. After a specific charging time with a unidirectional injection current, charge continuously accumulates on the electrode double layer of the supercapacitor, thereby accumulating and generating a defined dynamic energy storage capacity on the subsequent supercapacitor. Subsequently, the system directly measures the potential difference across the subsequent supercapacitor to convert the dynamically stored energy into a real-time potential state across the supercapacitor. Based on the fundamental physical principles of capacitors, the specific calculation process is as follows: Thus, the amplitude value is accurately converted and generated. supercapacitor voltage signal This signal will then be used as a key decision-making basis and input into the hysteresis comparator in real time to determine the voltage status.

[0064] S4. Perform hysteresis comparison processing on the supercapacitor voltage signal to generate a voltage state determination signal;

[0065] Optionally, the generated voltage state determination signal includes:

[0066] The supercapacitor voltage signal is compared with the upper threshold of the hysteresis comparator to generate a charge saturation state signal;

[0067] The supercapacitor voltage signal is compared with the lower threshold of the hysteresis comparator to generate a power depletion warning signal;

[0068] The charging saturation state signal and the power depletion warning signal are combined to perform state maintenance and reversal control, and a voltage state determination signal is generated.

[0069] Specifically, in order to convert the continuously changing supercapacitor voltage signal into a definite, jitter-free binary logic signal to drive subsequent power supply switching decisions, this step aims to generate a stable and reliable voltage state determination signal. The core of this process is the use of a hysteresis comparator to process the supercapacitor voltage signal. A hysteresis comparator is a special voltage comparison circuit with two different switching thresholds: an upper threshold and a lower threshold. This design effectively suppresses frequent output state jumps caused by small voltage fluctuations near the critical point, ensuring the stability of the control signal.

[0070] The process first involves acquiring the supercapacitor voltage signal in real time. As input to the hysteresis comparator. The system will Compared with the preset upper limit threshold Continuous comparison is performed. This upper limit threshold... Typically, a relatively high voltage value, such as 3.6 volts to 4.1 volts, is set, indicating that the supercapacitor has stored enough energy to independently power the sensing node. When charging... Rise and exceed When the comparator output flips to a high level, this state is the charge saturation signal, indicating that the energy reserve is sufficient.

[0071] Also in parallel Compared with the preset lower threshold Perform a comparison. This lower threshold. Set at a level lower than A voltage value, such as 2.7 volts to 3.0 volts, indicates that the supercapacitor is about to run out of energy and a backup power source is needed. This occurs when the sensor node consumes energy... Decline and below When the comparator output flips to a low level, this state is the power depletion warning signal, triggering a power supply switch warning.

[0072] By utilizing the inherent state hold and toggle control logic of the hysteresis comparator, and combining the charge saturation state signal and the depletion warning signal, the final voltage state determination signal is directly generated. The behavior logic of this signal is: once Exceed , It is then locked to a high level; thereafter, even It has fallen somewhat, as long as it does not fall below... , It will remain at a high level. Conversely, once... Break , It then locks to a low level; thereafter, even if energy harvesting causes... It has rebounded slightly, as long as it does not reach [a certain level] again. , It will remain at a low level. This mechanism ensures the voltage state determination signal... The state transition occurs only at two clearly defined voltage points, thus providing clear and unambiguous input instructions for subsequent hardware interlocking logic. Its logical behavior can be summarized as: when... > ,but Output high level; when < ,but Output low level; when ≤ ≤ ,but Keep its previous state unchanged.

[0073] For example, in the verification of the hysteresis comparison characteristics of a passive vibration sensing node, the system first uses the supercapacitor voltage signal generated in the previous step as the input to the hysteresis comparator, and continuously compares it with preset upper and lower threshold values ​​in real time. During the continuous operation phase of this field test, the upper threshold value of the hysteresis comparator... Set as lower threshold Set as When it is in the charging phase and the supercapacitor voltage signal Continued to rise and reached for the first time At that time, the system compares the supercapacitor voltage signal with the upper threshold of the hysteresis comparator. Because it detects... The comparator output immediately flips to a high level, accurately generating the charge saturation signal. Subsequently, when the node enters the RF transmission state, causing power consumption, the supercapacitor voltage signal... Gradually falling back to And eventually fell to At that time, the system compares the supercapacitor voltage signal with the lower threshold of the hysteresis comparator. Because it detects... The comparator output immediately flips to a low level, accurately generating a low-power warning signal. During this process, the control system integrates the charge saturation signal and the low-power warning signal for state maintenance and switching control. Based on the logical behavior defined in the manual, when the supercapacitor voltage signal is between two threshold values... When the voltage state determination signal remains unchanged from the previous state, the specific digital substitution and logic state change process is as follows: when At that time, according to This enables the voltage state determination signal ,when Falling back to At that time, according to This ensures that the voltage state determination signal remains in its original state. ,when Further decline to At that time, according to This causes the voltage state determination signal to flip to Ultimately, a voltage state determination signal without any switching jitter was stably generated through a clearly defined voltage state transition logic. This provides clear and unambiguous logical instructions for the power supply switching decisions of the subsequent hardware interlocking module.

[0074] S5. Receive the voltage state determination signal and perform hardware interlock logic processing to generate a power supply switching control signal. Based on the power supply switching control signal, prioritize scheduling the downstream supercapacitor to supply power to the passive vibration sensing node. When the supercapacitor's energy is insufficient, switch to the backup battery to supplement the power supply.

[0075] Optionally, the generation of the power supply switching control signal includes:

[0076] The voltage state determination signal is input into the hardware interlock module for level mutual exclusion processing to generate a first driving level and a second driving level.

[0077] The first driving level is applied to the control terminal of the first switching transistor connected to the subsequent supercapacitor, thereby controlling the first switching transistor to be turned on or off, forming the on or off state of the supercapacitor power supply path.

[0078] The second driving level is applied to the control terminal of the second switch tube connected to the backup battery, thereby controlling the second switch tube to be turned on or off, forming the on or off state of the backup battery power supply path.

[0079] Hardware interlocking logic ensures that the first and second switching transistors do not conduct simultaneously. Combined with the on / off states of the supercapacitor and backup battery, a power switching control signal for priority power supply scheduling is generated.

[0080] Specifically, the voltage state determination signal The input is fed into a hardware interlock module for level mutual exclusion processing. This module can be constructed from basic logic gates, such as an inverter, whose core task is to convert the input single signal into a single logic gate. This is converted into two drive levels with completely opposite logic states. As a result, the system generates a first drive level D1 and a second drive level D2. These two levels are electrically strictly mutually exclusive, that is, when D1 is high, D2 must be low, and vice versa.

[0081] A first drive level D1 is applied to the control terminal of the first switching transistor connected to the subsequent supercapacitor. This switching transistor is typically a P-channel MOSFET with extremely low on-resistance. When D1 is at a specific logic level, such as low, the switching transistor is turned on, thereby establishing the supercapacitor power supply path and allowing the supercapacitor to supply power to the load. Conversely, when D1 goes high, the switching transistor is turned off, cutting off this path.

[0082] The second drive level D2 is applied to the control terminal of the second switch transistor connected to the backup battery. This switch transistor is also a P-channel MOSFET. Since the logic level of D2 is always opposite to that of D1, when D1 is low, causing the first switch transistor to turn on, D2 must be high, thus keeping the second switch transistor off and forming the off state of the backup battery power supply path. Conversely, when D1 becomes high, causing the first switch transistor to turn off, D2 becomes low, turning on the second switch transistor and establishing the backup battery power supply path.

[0083] This hardware interlocking logic design ensures that the first and second switching transistors can never be turned on simultaneously, effectively avoiding power conflicts and potential loop current risks caused by direct connection between the downstream supercapacitor and the backup battery. The combined effect of the first and second drive levels, along with their determination of the on / off states of the downstream supercapacitor and backup battery, constitutes a complete power switching control signal for priority power supply scheduling. This signal is not a single electrical signal, but rather refers to the entire control mechanism that drives the two switching transistors and ensures their mutual exclusion.

[0084] For example, in the power supply switching control verification of the passive vibration sensing node, a hardware interlock module is connected to the system circuit for level mutual exclusion processing and path state control. The system first receives the voltage state determination signal generated in the previous step and inputs it into the hardware interlock module. In this test case, the current supercapacitor is set to have sufficient charge, and the input voltage state determination signal is in a high-level logic state. The hardware interlock module receives this signal and executes hardware interlock logic processing, using internal inverters and other logic gates to perform level mutual exclusion processing, accurately converting the single high-level input signal into two completely opposite drive levels, thereby smoothly generating a low-level first drive level and a high-level second drive level. Next, the system applies the low-level first drive level to the control terminal of the first switch connected to the subsequent supercapacitor. Since this switch is turned on at a low level, it correspondingly controls the first switch to turn on, successfully forming the conduction state of the supercapacitor power supply path. Simultaneously, the system applies the high-level second drive level to the control terminal of the second switch connected to the backup battery. Since the two levels are electrically mutually exclusive, this correspondingly controls the second switch to turn off, successfully establishing the off state of the backup battery power supply path. Through this hardware interlocking logic design of level mutual exclusion and timing coordination, it fundamentally ensures that the first and second switches never conduct simultaneously, eliminating the risk of power conflict caused by the simultaneous conduction of the power supply paths of the supercapacitor and the backup battery. Finally, the control system, combining the conduction state of the supercapacitor power supply path and the off state of the backup battery power supply path, stably generates a power switching control signal for priority power supply scheduling, safely and reliably achieving the intelligent scheduling goal of prioritizing the power supply of the supercapacitor and switching to the backup battery to supplement power when the supercapacitor's energy is insufficient.

[0085] Optionally, the step of inputting the voltage state determination signal into the hardware interlock module for level mutual exclusion processing to generate a first drive level and a second drive level includes:

[0086] Extract the rising edge and falling edge features of the voltage state determination signal to generate corresponding edge trigger pulses;

[0087] The dead time generation circuit along the trigger pulse is delayed and blocked to generate a dead time isolation signal for staggering the on and off timing of the switching transistor.

[0088] The dead zone isolation signal and the voltage state determination signal are superimposed and mutually exclusive logic operations are performed to generate a first driving level and a second driving level.

[0089] Specifically, a drive timing sequence with dead time is generated. Dead time is an extremely short delay window reserved to ensure that one switch is completely turned off before another begins to conduct, aiming to fundamentally prevent shoot-through short circuits caused by two power supply paths simultaneously turning on at the moment of switching. This process begins with the voltage state determination signal. The system captures dynamic characteristics by extracting rising edge and falling edge features from low to high or high to low through edge detection circuit. Whenever a valid level transition is detected, a narrow-band edge trigger pulse is generated.

[0090] This edge-triggered pulse is fed into a dead-time generation circuit. The core function of this circuit is to perform delayed blocking. Physical switches such as MOSFETs have turn-on and turn-off delays of tens to hundreds of nanoseconds. If the drive signal is simply inverted, a brief period of simultaneous conduction can easily occur. Therefore, when the dead-time generation circuit receives the edge-triggered pulse, it immediately generates a blocking signal with a preset duration, such as 100 to 500 nanoseconds. This blocking signal, also known as the dead-time isolation signal, forces the drive signals of both switches to be simultaneously inactive at the moment of power switching, ensuring that the switch about to be turned off has sufficient time to completely turn off.

[0091] The dead-zone isolation signal is compared with the original voltage state determination signal. A superposition mutual exclusion logic operation is performed to generate the final first drive level D1 and second drive level D2. This is typically implemented using combinational logic gates, whose logic rule is: in a non-switching stable state, the levels of D1 and D2 are determined by... Directly decide, and maintain mutual exclusivity. And... At the moment of the transition, the dead zone isolation signal is activated, which temporarily blocks the signal with the highest priority. The function of this is to force both D1 and D2 to output a non-conducting level. Only after the preset dead time has elapsed and the dead time isolation signal has been released, will the levels of D1 and D2 return to normal. The new state determines the timing. This "break-before-make" timing control ensures that the first drive level and the second drive level are not only mutually exclusive in steady state, but also do not overlap during dynamic switching, thus achieving the highest level of hardware interlocking.

[0092] For example, in the dynamic switching timing verification of a passive vibration sensing node, the system first captures and extracts the rising and falling edge characteristics of the input voltage state determination signal transitioning from low to high level in real time. In this field switching test example, the edge detection circuit accurately captures the instantaneous transition of the voltage state determination signal, and smoothly generates a pulse with a width of [missing information] at the trigger moment. A narrow-band edge-triggered pulse is generated. This pulse is then directly input into the dead-time generation circuit for delay blocking. To ensure the physical switch has sufficient and complete cutoff time and to eliminate potential overlap shoot-through risks, the internal blocking delay mechanism of the dead-time generation circuit forces the generation of a pulse with a duration of [duration missing]. A high-level blocking pulse is generated to stably generate a dead-zone isolation signal. Subsequently, the control system receives this dead-zone isolation signal and the original voltage state determination signal, and performs superimposed mutual exclusion logic operations on them. To quantitatively verify the control effect of this superimposed mutual exclusion logic on the output during dynamic switching, a high-level blocking pulse is generated after the trigger transition. During the dead-time delay window, the dead-time isolation signal is activated as a high-level blocking signal. Even if the voltage state determination signal has already transitioned to a high-level logic state, according to the superimposed mutual exclusion logic rule of "break first, then turn on," the dead-time isolation signal temporarily blocks the effect of the voltage state determination signal with the highest priority, forcing both the first and second drive levels to output a non-conducting high level, causing the two channel transistors connected to the P-channel MOSFETs to be simultaneously cut off at the moment of switching. Only within the preset... After the dead time ends, the dead-time isolation signal is released and returns to a low level. Only then are the first and second drive levels unshielded and completely determined by the new state of the voltage state determination signal. This causes the first drive level to flip to a low level to turn on the first switch, and the second drive level to remain high to turn off the second switch. This is achieved by forcibly generating [the signal] at the moment of switching. The timing control method of overlapping inactive drive signals successfully generates a first drive level and a second drive level that are mutually exclusive in steady state and have no overlap during dynamic switching, thus achieving the highest level of hardware interlocking.

[0093] Optionally, the step of prioritizing the use of a downstream supercapacitor to power the passive vibration sensing node based on the power supply switching control signal, and switching to a backup battery to supplement power when the supercapacitor's energy is insufficient, includes:

[0094] In response to the power supply switching control signal, the first switching transistor is turned on by default and the second switching transistor is turned off, so that the passive vibration sensing node is powered by the subsequent supercapacitor.

[0095] When the supercapacitor voltage signal drops to the lower limit threshold of the hysteresis comparator, it is determined that the energy storage is insufficient. The first switch is turned off and the second switch is turned on, and the backup battery is switched to power the sensing node.

[0096] When the supercapacitor voltage signal rises back to the upper limit threshold of the hysteresis comparator, it is determined that the energy storage is sufficient, the first switch is turned on again and the second switch is turned off, and the supercapacitor priority power supply mode is restored.

[0097] Specifically, in response to the power supply switching control signal, it executes its default priority power supply mode. This occurs during system initialization or when the downstream supercapacitor has sufficient energy, i.e., the supercapacitor voltage signal is higher than the upper threshold of the hysteresis comparator. At this time, the voltage status determination signal is high, which causes the power supply switching control signal to turn on the first switch and turn off the second switch by default. In this state, the power supply path of the downstream supercapacitor is established, and its stored energy is preferentially used to power the passive vibration sensing node, while the backup battery is in standby mode and does not consume power.

[0098] When the passive vibration sensing node continuously operates and consumes energy, it causes the supercapacitor voltage signal to... It continues to decline and eventually reaches the lower limit threshold of the hysteresis comparator. When this happens, the system determines that the main energy storage unit has insufficient energy. This threshold... Typically, the voltage is set above the minimum voltage required for normal node operation, such as 2.7 volts. At this point, the voltage status determination signal flips to a low level, and the power supply switching control signal responds immediately. After a dead time, it precisely turns off the first switch while simultaneously turning on the second switch. This switching action seamlessly switches the power source from the downstream supercapacitor to the backup battery, which then replenishes power to the sensing node, ensuring service continuity.

[0099] During backup battery operation, the energy harvesting module continues to operate, injecting the harvested vibration energy into the subsequent supercapacitor for charging via the pre-amplifier circuit. When the supercapacitor voltage signal... Therefore, it gradually recovers and eventually reaches the upper limit threshold of the hysteresis comparator again. When the system determines that the energy storage is sufficient and it has the ability to independently supply power again, the voltage status determination signal flips back to a high level, the power supply switching control signal responds again, turns off the second switch and turns the first switch back on, and the system returns to the initial mode where the downstream supercapacitor provides priority power supply, thus completing a complete adaptive power supply scheduling cycle.

[0100] For example, in the verification of power supply switching control execution of the passive vibration sensing node, the system first receives the power supply switching control signal generated in the previous step to start the adaptive scheduling program. During the first running cycle of system initialization, the current supercapacitor voltage signal is acquired in real time. Because the voltage is higher than the preset upper threshold of the hysteresis comparator. The system automatically recognizes that the main energy storage unit has sufficient energy and responds to the power supply switching control signal by executing the default priority power supply mode. It controls the first drive level to output a low level to default on the first switching transistor, while simultaneously controlling the second drive level to output a high level to turn off the second switching transistor. This successfully establishes the power supply path for the subsequent supercapacitor, which then prioritizes powering the passive vibration sensing node. At this time, the backup battery is in a non-consumption standby state. Next, the passive vibration sensing node enters a continuous radio frequency data transmission state, causing the charge in the subsequent supercapacitor to be rapidly consumed. The supercapacitor voltage signal is monitored to continuously decrease. When it drops to the lower threshold of the hysteresis comparator... Upon receiving the signal, the control system immediately determined that the main energy storage unit was insufficient, triggering a state flip mechanism. It quickly controlled the first drive level to switch high to turn off the first switch, and simultaneously controlled the second drive level to switch low to turn on the second switch. This successfully switched the power supply bus to the backup battery power supply path, allowing the backup battery to promptly supplement power to the sensing nodes and ensuring that the nodes were not disconnected due to power failure. Subsequently, the continuous vibration of the industrial water pump caused the piezoelectric transducer to resume efficient energy collection. Through charging, the supercapacitor voltage signal slowly recovered, reaching the upper limit threshold of the hysteresis comparator. When the system determines that the main energy storage unit has returned to the fully charged state, it triggers a new round of timing flip, pulls the first drive level low to turn on the first switch, and pulls the second drive level high to turn off the second switch, thereby cutting off the backup battery power supply path and fully restoring the supercapacitor priority power supply mode. This achieves the verification goal of adaptive closed-loop scheduling of power supply according to the main energy storage state.

[0101] Optionally, after generating the power switching control signal for priority power supply scheduling, the method further includes:

[0102] Obtain the stable power supply bus voltage formed under the action of the power supply switching control signal;

[0103] By utilizing the low equivalent series resistance of the subsequent supercapacitor, voltage drops caused by instantaneous high current are suppressed.

[0104] Dynamic smoothing compensation is performed on the power supply bus voltage to control the bus voltage fluctuation within the power supply requirement threshold, thereby generating a highly stable and smooth power supply voltage.

[0105] Specifically, the transient high current pulse and bus voltage smoothing compensation diagram is as follows: Figure 4 As shown, dynamic voltage regulation and instantaneous power compensation are performed on the final power supply bus. This process first involves acquiring the stable power supply bus voltage formed by the conduction of the first or second switching transistor under the action of the power supply switching control signal. This bus voltage is the sole source of power for all loads in the entire sensing node, including the microcontroller and RF module.

[0106] When the RF transmitter module of the passive vibration sensing node operates, it generates instantaneous high-current consumption pulses with extremely short durations, such as only a few milliseconds, but with extremely high current amplitudes, reaching peak values ​​of tens to hundreds of milliamperes. Without compensation, these current pulses flow through the internal resistance of the power supply, causing a momentary voltage drop in the stable power supply bus voltage. To solve this problem, the system utilizes a key physical characteristic of the downstream supercapacitor: its extremely low equivalent series resistance (ESR). ESR is a core parameter measuring the energy loss and voltage drop of a capacitor when providing high current; the ESR of a supercapacitor is typically at an extremely low level of tens of milliohms.

[0107] Regardless of whether it is currently powered by the supercapacitor itself or by the backup battery, this downstream supercapacitor is always physically connected to the power supply bus, acting as a huge local power buffer. When a sudden surge in current consumption occurs, the supercapacitor, with its equivalent series resistance far lower than that of the backup battery and other components in the power supply path, can instantly release the large current, actively absorbing the vast majority of the current surge. This physically limits the voltage drop to an extremely low level, rather than relying on the main power supply. This process constitutes dynamic smoothing compensation for the power supply bus voltage. This compensation effectively suppresses the magnitude of the voltage drop. Their relationship can be approximated as:

[0108]

[0109] in, This refers to the actual voltage drop on the power supply bus. It is the peak current of the "instantaneous high current consumption pulse" generated by the radio frequency module; This is the equivalent series resistance of the subsequent supercapacitor. Since the subsequent supercapacitor is directly connected in parallel to the power supply bus, its low resistance is crucial when dealing with instantaneous high current pulses. The characteristics determine the effective source resistance of the power supply network. ,Right now Through the parallel connection of subsequent supercapacitors, The value is reduced and approaches the equivalent series resistance of the supercapacitor, thus reducing the value of the supercapacitor. By controlling the voltage within an extremely small range at the millivolt level, a stable and smooth power supply voltage capable of withstanding transient load shocks is ultimately generated for the RF module and even the entire node, ensuring the reliability of data transmission and the overall stability of the system.

[0110] For example, in the verification of dynamic voltage regulation and power compensation of the power supply bus of the passive vibration sensing node, the system first obtains the stable power supply bus voltage formed by the conduction of the switching transistor under the action of the power supply switching control signal. When the radio frequency transmission module of the passive vibration sensing node is working, it generates a transient high current consumption pulse with an extremely short duration but an extremely high current amplitude. In the test example, the peak current of this pulse lasts for several milliseconds and the amplitude reaches Without compensation, the pulse current flowing through the power supply's internal resistance will cause a severe bus voltage drop. Therefore, given that this instantaneous large current is primarily responded to by the downstream supercapacitor physically connected in parallel to the power supply bus, the low equivalent series resistance of the downstream supercapacitor is utilized to suppress the voltage drop and handle transient loads. In the hardware selection, the equivalent series resistance parameter of this downstream supercapacitor was determined to be... When a sudden high-current pulse occurs, the large current is directly supplied by a supercapacitor with extremely low internal resistance. According to Ohm's law, the dynamic voltage drop caused by the pulse being consumed across the equivalent series resistance is significant. It objectively exists, and the corresponding substitution calculation process is as follows: Calculations show that the transient voltage drop it causes is extremely weak. This physical voltage drop cannot be completely eliminated, but its amplitude is only about one-thousandth of the bus voltage, within the system's normal ripple tolerance range. Subsequently, the system uses a dynamic voltage regulation circuit to dynamically smooth and compensate for the power supply bus voltage, performing real-time noise reduction and ripple suppression on the original bus voltage waveform containing a slight dip, further smoothing residual fluctuations and strictly controlling the overall fluctuation amplitude within the power supply requirement threshold. Finally, acknowledging the objective existence of this small physical voltage drop, the control system outputs a highly stable power supply voltage that meets the accuracy requirements of the microcontroller and RF module.

[0111] Based on the same inventive concept, such as Figure 5 As shown, the present invention also provides an adaptive power supply scheduling system for a passive vibration sensing node, the system comprising:

[0112] The energy harvesting and rectification module is used to acquire the original AC signal generated by the piezoelectric transducer based on the vibration of the industrial water pump, and to rectify the original AC signal and then introduce it into the front-stage energy storage capacitor for charge accumulation to generate the front-stage voltage signal.

[0113] Impedance matching and transformation module, used to perform impedance matching and voltage transformation on the front-end voltage signal to generate energy transfer current;

[0114] The supercapacitor voltage signal generation module is used to guide the energy transfer current into the subsequent supercapacitor for energy storage and generate a supercapacitor voltage signal.

[0115] The hysteresis comparison module is used to perform hysteresis comparison processing on the supercapacitor voltage signal to generate a voltage state determination signal.

[0116] The power supply switching execution module is used to receive the voltage status determination signal and perform hardware interlock logic processing to generate a power supply switching control signal. Based on the power supply switching control signal, it prioritizes scheduling the downstream supercapacitor to supply power to the passive vibration sensing node. When the supercapacitor's energy is insufficient, it switches to the backup battery to supplement the power supply.

[0117] It should be noted that the electrical connections between the various units described above do not necessarily represent direct or indirect connections. Any indirect connection method can be applied to the embodiments of the present invention as long as it achieves the purpose of the present invention. The above descriptions are merely exemplary embodiments of the present invention and should not be construed as limiting the scope of the present invention.

[0118] All equivalent changes and modifications made in accordance with the teachings of this invention are still within the scope of this invention. Those skilled in the art will readily conceive of other embodiments of this invention upon considering the specification and the disclosure of practical truth. This application is intended to cover any variations, uses, or adaptations of this invention that follow the general principles of this invention and include common knowledge or conventional techniques in the art not described herein.

Claims

1. An adaptive power supply scheduling method for a passive vibration sensing node, characterized in that, The method includes: The original AC signal generated by the piezoelectric transducer based on the vibration of the industrial water pump is acquired, and the original AC signal is rectified and then introduced into the front-stage energy storage capacitor for charge accumulation to generate the front-stage voltage signal. Impedance matching and voltage transformation are performed on the preceding voltage signal to generate an energy transfer current; The energy transfer current is guided to be injected into the subsequent supercapacitor for energy storage, generating a supercapacitor voltage signal; The supercapacitor voltage signal is subjected to hysteresis comparison processing to generate a voltage state determination signal; The system receives the voltage status determination signal and performs hardware interlock logic processing to generate a power supply switching control signal. Based on the power supply switching control signal, it prioritizes scheduling the downstream supercapacitor to supply power to the passive vibration sensing node. When the supercapacitor's energy is insufficient, it switches to the backup battery to supplement the power supply.

2. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 1, characterized in that, The generation of the pre-stage voltage signal includes: It receives the raw AC signal output from the piezoelectric transducer and performs full-wave rectification to generate a pulsating DC signal. The pulsating DC signal is focused onto the plates of the front-stage energy storage capacitor to continuously and slowly accumulate a weak charge, generating an initial accumulated charge. The potential difference formed across the front-stage energy storage capacitor by the initial accumulated charge is monitored to generate a front-stage voltage signal.

3. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 1, characterized in that, The generated energy transfer current includes: The preceding voltage signal is acquired and a voltage threshold is detected to generate a preceding activation trigger signal; In response to the pre-stage activation trigger signal, the switching converter is controlled to perform high-frequency chopping processing to generate a high-frequency pulse current. The high-frequency pulse current is smoothed and filtered, and the impedance of the energy input terminal and the load impedance of the output terminal are adaptively matched and electrically isolated to generate an energy transfer current.

4. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 1, characterized in that, The generation of the supercapacitor voltage signal includes: The energy transfer current is acquired and unidirectional conduction control is performed to generate a unidirectional injection current; The unidirectional injected current is guided into the subsequent supercapacitor for large-capacity energy buffer storage, generating dynamic energy storage capacity. The dynamic energy storage capacity is converted into the real-time potential state across the supercapacitor, generating a supercapacitor voltage signal.

5. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 1, characterized in that, The generated voltage state determination signal includes: The supercapacitor voltage signal is compared with the upper threshold of the hysteresis comparator to generate a charge saturation state signal; The supercapacitor voltage signal is compared with the lower threshold of the hysteresis comparator to generate a power depletion warning signal; The charging saturation state signal and the power depletion warning signal are combined to perform state maintenance and reversal control, and a voltage state determination signal is generated.

6. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 1, characterized in that, The generated power supply switching control signal includes: The voltage state determination signal is input into the hardware interlock module for level mutual exclusion processing to generate a first driving level and a second driving level. The first driving level is applied to the control terminal of the first switching transistor connected to the subsequent supercapacitor, thereby controlling the first switching transistor to be turned on or off, forming the on or off state of the supercapacitor power supply path. The second driving level is applied to the control terminal of the second switch tube connected to the backup battery, thereby controlling the second switch tube to be turned on or off, forming the on or off state of the backup battery power supply path. Hardware interlocking logic ensures that the first and second switching transistors do not conduct simultaneously. Combined with the on / off states of the supercapacitor and backup battery, a power switching control signal for priority power supply scheduling is generated.

7. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 6, characterized in that, The step of inputting the voltage state determination signal into the hardware interlock module for level mutual exclusion processing to generate a first driving level and a second driving level includes: Extract the rising edge and falling edge features of the voltage state determination signal to generate corresponding edge trigger pulses; The dead time generation circuit along the trigger pulse is delayed and blocked to generate a dead time isolation signal for staggering the on and off timing of the switching transistor. The dead zone isolation signal and the voltage state determination signal are superimposed and mutually exclusive logic operations are performed to generate a first driving level and a second driving level.

8. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 1, characterized in that, The process of prioritizing the use of a downstream supercapacitor to power the passive vibration sensing node based on the power supply switching control signal, and switching to a backup battery to supplement power when the supercapacitor's energy is insufficient, includes: In response to the power supply switching control signal, the first switching transistor is turned on by default and the second switching transistor is turned off, so that the passive vibration sensing node is powered by the subsequent supercapacitor. When the supercapacitor voltage signal drops to the lower limit threshold of the hysteresis comparator, it is determined that the energy storage is insufficient. The first switch is turned off and the second switch is turned on, and the backup battery is switched to power the sensing node. When the supercapacitor voltage signal rises back to the upper limit threshold of the hysteresis comparator, it is determined that the energy storage is sufficient, the first switch is turned on again and the second switch is turned off, and the supercapacitor priority power supply mode is restored.

9. The adaptive power supply scheduling method for a passive vibration sensing node according to claim 6, characterized in that, After generating the power switching control signal for priority power supply scheduling, the process further includes: Obtain the stable power supply bus voltage formed under the action of the power supply switching control signal; By utilizing the low equivalent series resistance of the subsequent supercapacitor, voltage drops caused by instantaneous high current are suppressed. Dynamic smoothing compensation is applied to the power supply bus voltage to control bus voltage fluctuations within the power supply requirement threshold, thereby generating a highly stable and smooth power supply voltage.

10. An adaptive power supply scheduling system for a passive vibration sensing node, applied to an adaptive power supply scheduling method for a passive vibration sensing node as described in any one of claims 1-9, characterized in that, The system includes: The energy harvesting and rectification module is used to acquire the original AC signal generated by the piezoelectric transducer based on the vibration of the industrial water pump, and to rectify the original AC signal and then introduce it into the front-stage energy storage capacitor for charge accumulation to generate the front-stage voltage signal. Impedance matching and transformation module, used to perform impedance matching and voltage transformation on the front-end voltage signal to generate energy transfer current; The supercapacitor voltage signal generation module is used to guide the energy transfer current into the subsequent supercapacitor for energy storage and generate a supercapacitor voltage signal. The hysteresis comparison module is used to perform hysteresis comparison processing on the supercapacitor voltage signal to generate a voltage state determination signal. The power supply switching execution module is used to receive the voltage status determination signal and perform hardware interlock logic processing to generate a power supply switching control signal. Based on the power supply switching control signal, it prioritizes scheduling the downstream supercapacitor to supply power to the passive vibration sensing node. When the supercapacitor's energy is insufficient, it switches to the backup battery to supplement the power supply.

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