A transceiver joint calibration method, device and computer readable storage medium

Abstract

The application discloses a transceiver joint calibration method, device and computer readable storage medium, relates to the technical field of signal processing, and comprises the following steps: in the current calibration period, a first calibration signal is generated by offsetting the receiving link damage amount in a target calibration signal output by a target receiver; the first calibration signal is multiplied by a complex exponential rotation factor generated by a preset frequency control word to shift the first calibration signal to a zero frequency baseband and generate a second calibration signal; a cascade damage amount carried by the second calibration signal is extracted, and the inverse of the cascade damage amount is coupled into a reference signal to be output to a target transmitter as a pre-compensation amount, so that pre-calibration of a to-be-calibrated signal in the next calibration period is realized in the current calibration period, and a full-link pre-calibration signal is obtained; wherein the cascade damage amount comprises a loss amount of a transmitting link of the target transmitter and a loss amount of a cascade channel formed by a space channel between the target transmitter and the target receiver.

Description

Technical Field

[0001] This application relates to the field of signal processing technology, and in particular to a transceiver joint calibration method, apparatus and computer-readable storage medium. Background Technology

[0002] Direct conversion architecture has become the mainstream solution for broadband wireless transceiver chips due to its elimination of analog intermediate frequency links, ease of digital integration, and lower power consumption and area. However, mismatch in the quadrature modulation and demodulation stages will directly fold over to the baseband, introducing a variety of linear impairments: on the receiver side, this manifests as image interference caused by quadrature amplitude / phase mismatch, and DC offset may block the channel in high-gain mode; on the transmitter side, it manifests as transmit image caused by quadrature mismatch and carrier leakage and adjacent channel spurious signals caused by local oscillator leakage.

[0003] In an integrated transceiver chip, linear impairments of the transmitter can usually only be observed through the receiver feedback path. However, linear impairments in the transmission and reception stages are coupled with each other, which can affect the performance of traditional calibration methods for single links and single mismatches in chip-level joint calibration schemes, thus affecting calibration efficiency and making calibration more complex. Summary of the Invention

[0004] The main objective of this application is to provide a transceiver joint calibration method, apparatus, and computer-readable storage medium, which aims to easily achieve efficient joint calibration of the receiver and transmitter.

[0005] This application provides a transceiver joint calibration method, the method comprising: In the current calibration cycle, a first calibration signal is generated by offsetting the receive link impairment in the target calibration signal output by the target receiver; By multiplying the first calibration signal by a complex exponential rotation factor generated by a preset frequency control word, the first calibration signal is shifted to the zero-frequency baseband, generating a second calibration signal; the frequency control word is the difference between the local oscillator frequency of the target transmitter and the local oscillator frequency of the target receiver. Extract the cascaded damage amount carried by the second calibration signal, and couple the inverse of the cascaded damage amount as a pre-compensation amount into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtain the full-link pre-calibration signal. The cascaded damage includes the loss of the transmission link of the target transmitter and the loss of the cascaded channel formed by the spatial channel between the target transmitter and the target receiver.

[0006] In one embodiment, the step of generating a first calibration signal in the current calibration cycle by offsetting the receive link impairment in the target calibration signal output by the target receiver baseband analog front end includes: By superimposing the target calibration signal of the current calibration period with the DC offset coefficient of the target receiver of the current calibration period, an initial calibration signal that has compensated for the DC bias of the target receiver is obtained; The instantaneous compensation value for the orthogonal mismatch of the target receiver is obtained by performing an inner product operation on the target receiver orthogonal mismatch coefficient vector of the current calibration period and the complex conjugate vector of the initial calibration signal. The first calibration signal is obtained by superimposing the instantaneous compensation value onto the initial calibration signal.

[0007] In one embodiment, the step of extracting the cascaded impairment quantity carried by the second calibration signal and coupling the negative of the cascaded impairment quantity as a pre-compensation quantity into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtaining the end-to-end pre-calibration signal, includes: The second calibration signal is converted into a complex conjugate vector, and the inner product operation is performed on the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount and the complex conjugate vector converted from the second calibration signal to obtain the pre-compensation amount of orthogonal mismatch in the cascaded channel. The pre-compensation amount is superimposed on the reference signal to be output to the target transmitter to obtain the reference signal with orthogonal mismatch pre-compensation; The DC offset coefficient corresponding to the cascaded damage is superimposed on the reference signal that has undergone orthogonal mismatch pre-compensation to obtain the full-link pre-calibration signal.

[0008] In one embodiment, the step of extracting the cascaded impairment quantity carried by the second calibration signal and coupling the negative of the cascaded impairment quantity as a pre-compensation quantity into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtaining the end-to-end pre-calibration signal, includes: By multiplying the second calibration signal by the reciprocal of the fixed propagation error, a cleaned observation signal that has been compensated for the fixed propagation error is generated; The purification observation signal is converted into a complex conjugate vector, and the inner product operation is performed on the orthogonal mismatch coefficient vector corresponding to the cascade damage amount and the complex conjugate vector converted from the purification observation signal to obtain the pre-compensation amount of orthogonal mismatch in the cascade channel. The pre-compensation amount is superimposed on the reference signal to be output to the target transmitter to obtain the reference signal with orthogonal mismatch pre-compensation; The DC offset coefficient corresponding to the cascaded damage is superimposed on the reference signal that has undergone orthogonal mismatch pre-compensation to obtain the full-link pre-calibration signal.

[0009] In one embodiment, the method further includes: During the initialization calibration period, a loopback path is constructed between the target transmitter and the target receiver, and a loopback calibration signal is injected into the target transmitter; After the loopback calibration signal passes sequentially through the target transmitter, the loopback path, and the target receiver, a loopback calibration response signal is obtained. The first loopback calibration signal is obtained by superimposing the loopback calibration response signal with the DC offset coefficient of the target receiver during the initial calibration period. The second loopback calibration signal is obtained by performing an inner product operation on the target receiver orthogonal mismatch coefficient vector of the initial calibration period and the complex conjugate vector of the first loopback calibration signal, and then superimposing the inner product operation result onto the first loopback calibration signal. By multiplying the second loopback calibration signal by a complex exponential rotation factor generated by the preset frequency control word, the second loopback calibration signal is shifted to the zero-frequency baseband, thereby generating a third loopback calibration signal. The DC offset coefficient corresponding to the cascaded damage amount within the initial calibration period is superimposed on the third loopback calibration signal to obtain the fourth loopback calibration signal; The fourth loopback calibration signal is converted into a complex conjugate vector. The orthogonal mismatch coefficient vector corresponding to the cascaded damage amount within the initial calibration period and the complex conjugate vector converted from the fourth loopback calibration signal are subjected to an inner product operation. The result of the inner product operation is superimposed on the fourth loopback calibration signal to obtain the fifth loopback calibration signal. The DC offset coefficient and quadrature mismatch coefficient vector of the target receiver during the initialization calibration period, and the DC offset coefficient and quadrature mismatch coefficient vector corresponding to the cascaded damage amount during the initialization calibration period are used as the initialization calibration reference damage coefficient and / or the initialization calibration reference damage coefficient vector.

[0010] In one embodiment, after the step of using the DC offset coefficient and quadrature mismatch coefficient vector of the target receiver during the initialization calibration period, and the DC offset coefficient and quadrature mismatch coefficient vector corresponding to the cascaded impairment amount during the initialization calibration period as the initialization calibration reference impairment coefficient and / or the initialization calibration reference impairment coefficient vector, the method further includes: Based on the loopback path, a complex DC signal is injected into the target transmitter; Based on the initial calibration reference impairment coefficient and / or the initial calibration reference impairment coefficient vector, the reference impairment amount contained in the feedback signal of the complex DC signal is compensated to obtain the complex DC calibration signal of the complex DC signal; the reference impairment amount includes the receive link impairment amount and the cascade impairment amount of the initial calibration period determined by the initial calibration reference impairment coefficient and / or the initial calibration reference impairment coefficient vector. The ratio of the complex DC calibration signal to the complex DC signal is used as the fixed transmission error.

[0011] In one embodiment, the method further includes: In the current calibration cycle, the calibration error value and / or calibration error value vector corresponding to each iteration during the iterative calibration of the target calibration signal are obtained; Based on the calibration error value and / or calibration error value vector corresponding to each iteration, update the DC offset coefficient and / or orthogonal mismatch coefficient vector corresponding to the cascaded damage in the current calibration cycle; And / or, based on the calibration error value and / or calibration error value vector corresponding to each iteration, update the DC offset coefficient and / or quadrature mismatch coefficient vector of the target receiver in the current calibration cycle.

[0012] In one embodiment, the method further includes: Divide the value of each error feedback quantity by its respective modulus to obtain the error feedback quantity per unit amplitude. For any of the error feedback quantities, if the data type of the error feedback quantity is the signal value of the signal after compensation or pre-compensation of DC bias, then the first modulus value of the arithmetic mean of the error feedback quantity per unit amplitude is calculated. If the data type of the error feedback quantity is the signal value of the signal after compensation or pre-compensation orthogonal mismatch, calculate the second modulus value of the arithmetic mean of the square of the error feedback quantity per unit amplitude; When the first modulus or the second modulus is lower than the preset convergence threshold, the calibration error value and / or calibration error value vector corresponding to the error feedback quantity is used as the calibration error value and / or calibration error value vector at the next moment.

[0013] In addition, to achieve the above objectives, this application also provides a transceiver joint calibration device, which includes: a memory, a processor, and a computer program stored in the memory and executable on the processor, the computer program being configured to implement the transceiver joint calibration method as described above.

[0014] In addition, to achieve the above objectives, this application also provides a computer-readable storage medium storing a computer program that, when executed by a processor, implements the transceiver joint calibration method as described above.

[0015] This application provides a transceiver joint calibration method. By canceling the receive link impairment in the target calibration signal output by the target receiver to obtain a first calibration signal, the first calibration signal is digitally down-converted to obtain a second calibration signal shifted to the zero-frequency baseband. Then, a pre-compensation signal with the opposite of the cascaded impairment is superimposed on the reference signal to be output to the target transmitter to obtain a full-link pre-calibration signal, which is output to the RF front-end of the transmitter. This allows for the pre-calibration of the signal to be calibrated in the next calibration cycle in the current calibration cycle, thus achieving efficient joint calibration of the receiver and transmitter in a simple way.

[0016] This application utilizes the local oscillator frequency difference between the transmitter and receiver to place the linear impairments of the transmitter and receiver at separable digital frequency points. By shifting the frequency band, two calibration links can operate in parallel without contaminating each other, and joint calibration of receiver DC offset and quadrature mismatch, as well as transmitter DC offset and quadrature mismatch can be performed, thereby improving the efficiency and accuracy of transceiver calibration. Attached Figure Description

[0017] The accompanying drawings, which are incorporated in and form part of this specification, illustrate embodiments consistent with this application and, together with the description, serve to explain the principles of this application.

[0018] To more clearly illustrate the technical solutions in the embodiments of this application or the prior art, the drawings used in the description of the embodiments or the prior art will be briefly introduced below. Obviously, for those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0019] Figure 1 This is a schematic flowchart of the transceiver joint calibration method provided in the first embodiment of this application; Figure 2 A schematic flowchart illustrating the transceiver joint calibration method provided in the second embodiment of this application; Figure 3 A schematic flowchart illustrating the transceiver joint calibration method provided in the third embodiment of this application; Figure 4 This is a schematic flowchart of the transceiver joint calibration method provided in the fourth embodiment of this application; Figure 5 This is a schematic diagram of the signal flow during the initialization calibration phase provided in an embodiment of this application; Figure 6This is a schematic diagram of the signal flow during the fixed transmission error calibration stage provided in an embodiment of this application; Figure 7 A schematic diagram of the actual calibration stage provided in the embodiments of this application; Figure 8 This is a schematic diagram of the signal flow during the actual calibration stage provided in the embodiments of this application; Figure 9 This is a schematic diagram of the hardware operating environment involved in the embodiments of this application.

[0020] The purpose, features, and advantages of this application will be further explained in conjunction with the embodiments and with reference to the accompanying drawings. Detailed Implementation

[0021] It should be understood that the specific embodiments described herein are merely illustrative of the technical solutions of this application and are not intended to limit this application.

[0022] To better understand the technical solution of this application, a detailed description will be provided below in conjunction with the accompanying drawings and specific implementation methods.

[0023] The subject of the transceiver joint calibration method of this application can be a transceiver joint calibration device with data processing, network communication and program operation functions. For example, it can be a control system, control circuit, etc. that can realize the above functions. This embodiment does not specifically limit it.

[0024] The following description uses a transceiver joint calibration device as the main execution unit to illustrate the various embodiments.

[0025] This application presents a transceiver joint calibration method according to a first embodiment. Please refer to [link / reference]. Figure 1 The transceiver joint calibration method may include steps S10 to S30: Step S10: In the current calibration cycle, a first calibration signal is generated by offsetting the receive link impairment in the target calibration signal output by the target receiver.

[0026] The current calibration period is the time window for impairment extraction and adaptive coefficient update of the currently received signal. The target receiver refers to the received signal processing link entity in the RF transceiver system, and is the object to be calibrated in the various embodiments of this application. The physical boundary of the target receiver extends from the antenna interface or RF input port to the digital output of the analog-to-digital converter, encompassing the RF front-end (including low-noise amplifiers and RF filters), down-conversion mixer, local oscillator circuit, baseband analog front-end, and analog-to-digital converter. In the transceiver joint calibration method of this application, the output signal of the target receiver serves as the external input source of the transceiver joint calibration system, used to extract the impairment characteristics of each link.

[0027] The target calibration signal refers to the digital baseband sampling sequence output by the analog signal received by the target receiver and transmitted by the target transmitter after quantization by an analog-to-digital converter. It serves as the input source to be processed in the transceiver joint calibration method of this application. The target calibration signal carries the original transmitter information, spatial channel response, and distortions introduced by the non-ideal characteristics of the receiving link itself, and is the original basis for subsequent impairment extraction and calibration compensation. The amount of receiving link impairment refers to the deterministic distortion component in the target calibration signal introduced by the non-ideal physical characteristics of the target receiver.

[0028] In one feasible implementation, step S10 includes steps S11 to S13: Step S11: By superimposing the target calibration signal of the current calibration period with the target receiver DC offset coefficient of the current calibration period, an initial calibration signal with compensated target receiver DC bias is obtained.

[0029] The DC offset coefficient of the target receiver refers to the numerical compensation parameter used to compensate for the DC offset impairment carried by the target receiver's receiving link within the current calibration period. It represents the negative of the estimated DC offset of the receiving link at the current moment. The initial calibration signal is an intermediate signal state obtained by superimposing the target calibration signal and the target receiver's DC offset coefficient for the current calibration period, after removing the target receiver's DC offset component.

[0030] Understandably, the initial calibration signal is used to characterize the signal state in the target calibration signal where the damage caused by the DC offset of the target receiver link has been offset by the compensation parameters. However, the signal may still contain other damage, requiring further processing in subsequent calibration stages. The initial calibration signal is calculated as shown in Formula 1 below: Formula 1 in, Indicates the initial calibration signal. This indicates the target calibration signal for the current calibration cycle. This represents the DC offset coefficient of the target receiver in the current calibration period.

[0031] In practical applications, to ensure that the DC offset coefficient of the target receiver can quickly approach the actual damage value, the DC offset coefficient of the target receiver in the current calibration period can be updated in real time using an adaptive iterative algorithm. The calculation method is shown in Formula 2 below: Formula 2 in, This represents the target receiver DC offset coefficient for the next calibration cycle. This represents the iteration step size factor of the pre-set target receiver DC offset coefficient. It serves as the initial calibration signal in Formula 1, and also as the error feedback quantity driving the coefficient update in the current calibration cycle.

[0032] Furthermore, when the DC offset coefficient of the target receiver gradually approaches the optimal value through multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the first-order statistics of the residual signal to calculate the initial calibration signal. The normalized ratio of the arithmetic mean modulus to the average power over N sampling points is used as a measure of the residual DC offset of the target receiver.

[0033] First, calculate the ratio of the initial calibration signal value to the initial calibration signal magnitude to obtain the error feedback per unit amplitude of the initial calibration signal at one sampling point. Then, calculate the average of the error feedback per unit amplitude of N sampling points in the current calibration period to obtain the normalized statistical decision quantity (i.e., the first modulus of the arithmetic mean of the error feedback per unit amplitude of the initial calibration signal in the current calibration period) used to quantify the severity of the residual DC bias of the target receiver. The calculation method of the normalized statistical decision quantity used to quantify the severity of the residual DC bias of the target receiver is shown in Formula 3 below: Formula 3 in, It is a normalized statistical decision quantity used to quantify the severity of residual DC bias in a target receiver. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the DC offset coefficient of the target receiver has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0034] Step S12: The instantaneous compensation value of the target receiver's orthogonal mismatch is obtained by performing an inner product operation on the target receiver's orthogonal mismatch coefficient vector of the current calibration period and the complex conjugate vector of the initial calibration signal.

[0035] The target receiver quadrature mismatch coefficient vector refers to the complex coefficient vector used to compensate for the quadrature mismatch impairment carried by the target receiver's receiving link within the current calibration period. It corresponds to the number of taps in the signal processing link and represents the compensation estimate for the quadrature amplitude / phase imbalance of the receiving link at the current moment. Quadrature mismatch refers to the deviation of quadrature signals in amplitude gain and phase orthogonality, manifested as image spectrum leakage. The complex conjugate vector of the initial calibration signal refers to the vector sequence formed by taking the complex conjugate of the initial calibration signal at the current sampling point. The instantaneous compensation value of the target receiver quadrature mismatch is used to compensate for the image component of the target receiver link's quadrature mismatch in the current calibration period. The inner product operation refers to performing a vector dot product between the target receiver quadrature mismatch coefficient vector at the current moment and the complex conjugate vector of the initial calibration signal, i.e., a mathematical operation of multiplying corresponding elements and then summing them. The instantaneous compensation value of the target receiver quadrature mismatch is a complex digital correction quantity used to characterize the instantaneous reverse voltage vector that compensates for the quadrature phase and gain imbalance at the current moment.

[0036] Step S13: The first calibration signal is obtained by superimposing the instantaneous compensation value onto the initial calibration signal.

[0037] The first calibration signal is the target calibration signal after removing the target receiver's DC offset component and the quadrature mismatch image component. The first calibration signal is calculated using the following formula: Formula 4 in, This refers to the first calibration signal. This is the initial calibration signal from Formula 1. It is the target receiver orthogonal mismatch coefficient vector for the current calibration period. It is the complex conjugate vector of the initial calibration signal.

[0038] In practical applications, to ensure that the orthogonal mismatch coefficient vector of the target receiver can quickly approximate the true damage value, the orthogonal mismatch coefficient vector of the target receiver in the current calibration period can be updated in real time using an adaptive iterative algorithm. The calculation method is shown in Formula 5 below: Formula 5 in, This represents the target receiver orthogonal mismatch coefficient vector for the next calibration cycle. This represents the target receiver orthogonal mismatch coefficient vector for the current calibration period. It is the iteration step size matrix of the orthogonal mismatch coefficient vector at the target receiver, used to control the speed and stability of coefficient convergence along the gradient direction. It is the sequence of the first calibration signal in the current calibration cycle. The first calibration signal obtained from Equation 4 is used as the error feedback quantity to drive the coefficient update in the current calibration cycle.

[0039] Furthermore, when the orthogonal mismatch coefficient vector of the target receiver gradually approaches the optimal value through multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the second-order statistics of the residual signal to calculate the first calibration signal. The normalized ratio of the conjugate second-order moment modulus values ​​to the average power at N sampling points is used as a measure of the residual orthogonal mismatch of the target receiver.

[0040] First, calculate the ratio of the value of the first calibration signal to its magnitude to obtain the error feedback amount per unit amplitude of the first calibration signal at one sampling point. Then, calculate the average of the squares of the error feedback amounts per unit amplitude at N sampling points in the current calibration period to obtain the normalized statistical decision quantity (i.e., the second modulus of the arithmetic mean of the squares of the error feedback amounts per unit amplitude of the first calibration signal in the current calibration period) used to quantify the severity of residual quadrature mismatch in the target receiver. The calculation method of the normalized statistical decision quantity used to quantify the severity of residual quadrature mismatch in the target receiver is shown in Formula 6 below: Formula 6 in, It is a normalized statistical decision metric used to quantify the severity of residual orthogonal mismatch in the target receiver. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the orthogonal mismatch coefficient vector of the target receiver has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0041] This implementation achieves step-by-step cancellation of time-varying impairments in the target receiver's receiving link before the signal enters the frequency band shift, ensuring that the feedback observations of subsequent stages no longer contain the non-ideal characteristics of the target receiver itself, and providing a clean signal starting point for the accurate extraction of cascaded impairments.

[0042] Step S20: By multiplying the first calibration signal with a complex exponential rotation factor generated by a preset frequency control word, the first calibration signal is shifted to the zero-frequency baseband to generate the second calibration signal.

[0043] The frequency control word is the core digital parameter driving the numerically controlled oscillator (CNC oscillator), used to control the frequency of the CNC oscillator's output signal. The complex exponential twitch factor is the core mathematical sequence driving the digital mixer to perform spectrum shifting. It is a set of complex exponential function values ​​generated in real time by the CNC oscillator, and physically represents the unit rotation vector that changes with time on the orthogonal complex plane.

[0044] In practical applications, the frequency control word can be set to the difference between the target transmitter's local oscillator frequency and the target receiver's local oscillator frequency, calculated as shown in Formula 7 below: Formula 7 in, For frequency control word, It is the local angular frequency of the target transmitter. This is the local oscillator frequency of the target receiver. At this point, the complex exponential twitch factor is... Where n is the discrete sampling point index, representing the nth sampling point counted from the start time. It is the number of sample points collected per second, used to characterize the operating clock frequency of an analog-to-digital converter or a digital-to-analog converter.

[0045] Understandably, linear shifting of the signal spectrum (up-conversion or down-conversion) is achieved by performing complex multiplication on the input baseband or intermediate frequency signal sample by sample by sample using a complex exponential twitch factor. The instantaneous phase of the complex exponential twitch factor is generated by linear accumulation of a phase accumulator driven by a frequency control word, and the direction of rotation (sign) determines the direction of spectrum shifting. Shifting the first calibration signal to the zero-frequency baseband yields a second calibration signal in complex signal form that can be directly processed for baseband, providing a unified baseband analysis benchmark for subsequent processing.

[0046] Step S30: Extract the cascaded damage amount carried by the second calibration signal, and couple the inverse of the cascaded damage amount as a pre-compensation amount into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtain the full-link pre-calibration signal.

[0047] Cascaded damage includes the loss of the transmission link of the target transmitter and the loss of the cascaded channel formed by the spatial channel between the target transmitter and the target receiver. The spatial channel refers to the physical path and electromagnetic environment experienced by the signal as it propagates through space between the transmitter and receiver antennas, encompassing actual wireless transmission characteristics such as multipath fading, path loss, and Doppler shift. Pre-compensation is an inverse distortion vector artificially superimposed on the digital baseband of the transmitting end before the signal enters the non-ideal transmission link, i.e., the transmitter analog front-end and the spatial channel. The target transmitter refers to the entity of the transmit signal processing link in the RF transceiver system, and is the object to be calibrated in the various embodiments of this application. The physical boundary of the target transmitter extends from the input of the digital-to-analog converter to the antenna interface or RF output port, encompassing the digital-to-analog converter, baseband analog front-end (including reconstruction filters and buffer stages), up-conversion mixer, local oscillator circuit, and RF front-end (including RF filters and power amplifiers). The next calibration cycle is the time window during which the pre-compensation coefficients obtained in the previous cycle (i.e., the current calibration cycle) are applied to the signal block to be transmitted to compensate for cascaded damage. The end-to-end pre-calibration signal is a pre-compensation signal for the expected calibration signal in the next calibration cycle. It is sent to the input of the digital-to-analog converter of the target transmitter, and after being up-converted and amplified by the target transmitter's own analog link, it is radiated by the antenna. It does not change any parameters of the internal analog circuit of the transmitter, but only indirectly compensates for the damage introduced by the transmission link for the expected calibration signal in the next cycle by adjusting the pre-distortion of the baseband signal.

[0048] Understandably, this step decouples channel estimation from signal transmission in time, allowing the observation of current results to guide the pre-distortion processing of future signals, thereby optimizing the pre-equalization at the transmitter without consuming additional communication resources.

[0049] In one feasible implementation, step S30 includes steps S31 to S33: Step S31: Convert the second calibration signal into a complex conjugate vector, and perform an inner product operation on the orthogonal mismatch coefficient vector corresponding to the cascade damage amount and the complex conjugate vector converted from the second calibration signal to obtain the pre-compensation amount of orthogonal mismatch in the cascade channel.

[0050] The orthogonal mismatch coefficient vector corresponding to the cascaded impairment is a complex weighted vector used to characterize the degree of orthogonal amplitude and phase imbalance in the cascaded response of the transmit link and the space channel, mapping the orthogonal mismatch state of the current cascaded channel. The pre-compensation amount for orthogonal mismatch is a complex instantaneous correction value used to characterize a pre-distortion vector that is equal in magnitude and opposite in direction to the cascaded orthogonal mismatch. When superimposed on the reference signal, it can cancel the image interference introduced by the transmit link and the channel in advance.

[0051] Step S32: The pre-compensation amount is superimposed on the reference signal to be output to the target transmitter to obtain the reference signal with orthogonal mismatch pre-compensation.

[0052] The formula for calculating the reference signal after orthogonal mismatch pre-compensation is shown in Formula 8 below: Formula 8 in, The reference signal is pre-compensated for orthogonal mismatch. This is the reference signal to be output to the target transmitter. It is the pre-compensation amount for orthogonal mismatch in cascaded channels. It is the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount. It is the second calibration signal. , It is the complex conjugate vector converted from the second calibration signal.

[0053] It is understandable that the first calibration signal has already compensated for the DC offset from the target receiver's receiving link before the spectrum shift, so the second calibration signal does not affect the orthogonal mismatch pre-compensation from the cascaded channel.

[0054] In practical applications, to ensure that the orthogonal mismatch coefficient vector of the cascaded channels can quickly approximate the true damage value, an adaptive iterative algorithm can be used to update the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the current calibration cycle in real time. The calculation method is shown in Formula 9 below: Formula 9 in, This represents the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the next calibration cycle. This represents the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the current calibration cycle. It is a preset iteration step size matrix for the orthogonal mismatch coefficient vector corresponding to the cascaded damage, used to control the speed and stability of coefficient convergence along the gradient direction. It is the sequence of the second calibration signal in the current calibration cycle. It serves as the second calibration signal and also as the error feedback quantity driving the coefficient update for the current calibration cycle.

[0055] Furthermore, when the orthogonal mismatch coefficient vector corresponding to the cascaded damage gradually approaches the optimal value through multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalization decision method based on the second-order statistics of the residual signal to calculate the second calibration signal. The normalized ratio of the conjugate second-order moment magnitude to the average power at N sampling points is used as a measure of the residual orthogonal mismatch of the cascaded channels.

[0056] First, calculate the ratio of the value of the second calibration signal to its magnitude to obtain the error feedback amount per unit amplitude of the second calibration signal at one sampling point. Then, calculate the average of the squared error feedback amounts per unit amplitude of N sampling points in the current calibration period to obtain the normalized statistical decision quantity (i.e., the second modulus of the arithmetic mean of the squared error feedback amounts per unit amplitude of the second calibration signal in the current calibration period) used to quantify the severity of residual orthogonal mismatch in the cascaded channel. The calculation method of the normalized statistical decision quantity used to quantify the severity of residual orthogonal mismatch in the cascaded channel is shown in Formula 10 below: Formula 10 in, It is a normalized statistical decision metric used to quantify the severity of residual orthogonal mismatch in cascaded channels. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the orthogonal mismatch coefficient of the cascaded channel has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0057] Step S33: The DC offset coefficient corresponding to the cascaded damage is superimposed on the reference signal that has been pre-compensated for quadrature mismatch to obtain the full-link pre-calibration signal.

[0058] The calculation formula for the end-to-end pre-calibration signal is shown in Formula 11 below: Formula 11 in, It is a full-link pre-calibration signal. It is the reference signal obtained by orthogonal mismatch pre-compensation as shown in Formula 8. It is the DC offset coefficient corresponding to the cascaded damage.

[0059] In practical applications, to ensure that the DC offset coefficient of the cascaded channels can quickly approximate the actual damage value, the DC offset coefficient of the cascaded channels in the current calibration cycle can be updated in real time using an adaptive iterative algorithm, calculated as shown in Formula 12 below: Formula 12 in, This represents the DC offset coefficient of the cascaded channels in the next calibration cycle. The iteration step size factor represents the DC offset coefficient of the pre-set cascaded channels. It is the second calibration signal, and at the same time, it serves as the error feedback quantity for the current calibration cycle to drive coefficient updates.

[0060] Furthermore, when the DC offset coefficient of the cascaded channel gradually approaches the optimal value after multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the first-order statistics of the residual signal to calculate the second calibration signal. The normalized ratio of the arithmetic mean modulus to the average power at N sampling points is used as a measure of the residual DC offset of the cascaded channel.

[0061] First, calculate the ratio of the value of the second calibration signal to its magnitude to obtain the error feedback amount per unit amplitude of the second calibration signal at one sampling point. Then, calculate the average value of the error feedback amounts per unit amplitude for N sampling points in the current calibration period to obtain the normalized statistical decision quantity (i.e., the first modulus of the arithmetic mean of the error feedback amounts per unit amplitude of the second calibration signal in the current calibration period) used to quantify the severity of the residual DC bias in the cascaded channel. The calculation method of the normalized statistical decision quantity used to quantify the severity of the residual DC bias in the cascaded channel is shown in Formula 13 below: Formula 13 in, It is a normalized statistical decision quantity used to quantify the severity of residual DC bias in cascaded channels. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the DC offset coefficient of the cascaded channel has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0062] This implementation pre-constructs a distorted waveform with the same amplitude and opposite phase as the cascaded damage, so that the signal carries the pre-distortion before entering the transmitter's RF front end. After subsequent analog link and spatial transmission, the pre-compensation amount cancels out the cascaded damage, thereby achieving calibration of the cascaded channel damage.

[0063] Based on the above, this embodiment constructs a pre-compensation amount that is equivalent to and inversely proportional to the transmission link and spatial channel impairments within the current calibration cycle by canceling the receiver link impairments, shifting the frequency band, and extracting cascaded impairments at the target receiver. This pre-compensation amount is then coupled into the reference signal to be transmitted in the next calibration cycle, so that the signal carries pre-distortion before entering the target transmitter. This achieves joint optimization of pre-equalization at the transmitter and post-compensation at the receiver in the timing recursion between calibration cycles, ultimately improving the transmission quality of the entire link signal.

[0064] Based on the first embodiment described above, a second embodiment of the transceiver joint calibration method of this application is proposed. In the second embodiment, referring to... Figure 2 Before step S10, steps A10 to A80 may also be included: Step A10: During the initial calibration period, construct the loopback path between the target transmitter and the target receiver, and inject the loopback calibration signal into the target transmitter.

[0065] The loopback path refers to an artificial closed-loop link that directly connects the RF output of the target transmitter to the RF input of the target receiver via physical coupling (such as cables or internal feedback loops within a chip). The loopback calibration signal refers to the baseband sequence with known characteristics of the target transmitter input during the initialization calibration phase. This sequence drives adaptive iteration and fixed propagation error calibration under the loopback path. The loopback calibration signal can be a single-carrier signal. The initialization calibration phase refers to the process of initializing and calibrating the transceiver joint calibration system within the initialization calibration period.

[0066] By establishing an artificial closed loop to replace the actual space channel transmission, the impairment characteristics of the transmit link, receive link, and signal calibration processing link are separated under controlled conditions. This completes the initial convergence of the non-ideal characteristics of the transceiver's analog front end and the calibration of the fixed transmission error, providing an accurate benchmark reference for joint calibration in actual communication scenarios.

[0067] Step A20: After the loopback calibration signal passes sequentially through the target transmitter, the loopback path, and the target receiver, the loopback calibration response signal is obtained.

[0068] The loopback calibration response signal refers to the digital baseband sequence output by the analog-to-digital converter after the loopback calibration signal has undergone up-conversion and amplification at the target transmitter's RF front-end, loopback path transmission, and down-conversion and digitization at the target receiver's RF front-end. It carries cascaded information on target transmitter link impairments, receiver link impairments, and loopback path transmission characteristics, serving as the original observation sample for iterating initial coefficients and extracting fixed transfer errors during the initialization calibration phase. Fixed transfer error refers to the fixed non-ideal characteristic impairments carried by the target calibration signal on its transmission path before pre-compensation in the cascaded channels.

[0069] Step A30: The first loopback calibration signal is obtained by superimposing the loopback calibration response signal with the DC offset coefficient of the target receiver during the initialization calibration period.

[0070] The formula for calculating the first loopback calibration signal is shown in Formula 14 below: Formula 14 in, This is the first loopback calibration signal. It's understandable that, compared to the loopback calibration response signal, the first loopback calibration signal has already compensated for the DC bias impairment caused by the target receiver during the initialization calibration phase. It is the loopback calibration response signal. It is the DC offset coefficient of the target receiver during the initial calibration cycle.

[0071] In practical applications, to ensure that the DC offset coefficient of the target receiver during the initial calibration period can quickly approach the actual damage value, an adaptive iterative algorithm can be used to update the DC offset coefficient of the target receiver during the initial calibration period in real time. The calculation method is shown in Formula 15 below: Formula 15 in, This represents the DC offset coefficient of the target receiver in the next initialization calibration cycle. This represents the iteration step size factor of the target receiver DC offset coefficient during the pre-set initialization calibration period. It serves as the first loopback calibration signal in Equation 14, and also as the error feedback quantity driving the coefficient update during the initial calibration cycle.

[0072] Furthermore, when the DC offset coefficient of the target receiver during the initial calibration cycle gradually approaches the optimal value after multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the first-order statistics of the residual signal to calculate the first loopback calibration signal. The normalized ratio of the arithmetic mean modulus to the average power over N sampling points is used as a measure of the residual DC offset of the target receiver during the initial calibration period.

[0073] First, calculate the ratio of the value of the first loopback calibration signal to the magnitude of the first loopback calibration signal to obtain the error feedback amount per unit amplitude of the first loopback calibration signal at one sampling point. Then, calculate the average value of the error feedback amounts per unit amplitude at N sampling points during the initialization calibration period to obtain the normalized statistical decision quantity (i.e., the first modulus of the arithmetic mean of the error feedback amounts per unit amplitude of the first loopback calibration signal during the initialization calibration period) used to quantify the severity of the residual DC bias in the target receiver during the initialization calibration period. The calculation method of the normalized statistical decision quantity used to quantify the severity of the residual DC bias in the target receiver during the initialization calibration period is shown in Formula 16 below: Formula 16 in, It is a normalized statistical decision quantity used to quantify the severity of residual DC bias in the target receiver during the initialization calibration period. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the DC offset coefficient of the target receiver in the initial calibration cycle has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0074] Step A40: The second loopback calibration signal is obtained by performing an inner product operation on the target receiver orthogonal mismatch coefficient vector of the initial calibration period and the complex conjugate vector of the first loopback calibration signal, and then superimposing the inner product operation result onto the first loopback calibration signal.

[0075] The formula for calculating the second loopback calibration signal is shown in Formula 17 below: Formula 17 in, The second loopback calibration signal, as understood, compensates for the orthogonal mismatch loss of the target receiver during the initial calibration period, compared to the first loopback calibration signal. This is the first loopback calibration signal. This is the initialization calibration period, and the orthogonal mismatch coefficient vector of the target receiver. It is the complex conjugate vector of the first loopback calibration signal.

[0076] In practical applications, to ensure that the orthogonal mismatch coefficient vector of the target receiver during the initial calibration period can quickly approximate the true damage value, an adaptive iterative algorithm can be used to update the orthogonal mismatch coefficient vector of the target receiver during the initial calibration period in real time. The calculation method is shown in Formula 18 below: Formula 18 in, This represents the target receiver orthogonal mismatch coefficient vector for the next initialization calibration cycle. This represents the orthogonal mismatch coefficient vector of the target receiver during the initialization calibration period. It is the iteration step size matrix of the orthogonal mismatch coefficient vector corresponding to the target receiver in the pre-set initialization calibration period, used to control the speed and stability of coefficient convergence along the gradient direction. It is the sequence of the second loopback calibration signal in the initialization calibration cycle. The second loop calibration signal obtained from Formula 17 is used as the error feedback quantity to drive coefficient updates during the initial calibration cycle.

[0077] Furthermore, when the orthogonal mismatch coefficient vector of the target receiver during the initial calibration period gradually approaches the optimal value through multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the second-order statistics of the residual signal to calculate the second loopback calibration signal. The normalized ratio of the conjugate second-order moment modulus values ​​to the average power at N sampling points is used as a measure of the residual orthogonal mismatch of the target receiver during the initial calibration period.

[0078] First, calculate the ratio of the value of the second loopback calibration signal to the magnitude of the second loopback calibration signal to obtain the error feedback amount per unit amplitude of the second loopback calibration signal at one sampling point. Then, calculate the average of the squared error feedback amounts per unit amplitude at N sampling points during the initial calibration period. This yields the normalized statistical decision quantity (i.e., the second modulus of the arithmetic mean of the squared error feedback amounts per unit amplitude of the second loopback calibration signal at N sampling points during the initial calibration period) used to quantify the severity of the residual orthogonal mismatch of the target receiver during the initial calibration period. The calculation method for the normalized statistical decision quantity used to quantify the severity of the residual orthogonal mismatch of the target receiver during the initial calibration period is shown in Formula 19 below: Formula 19 in, It is a normalized statistical decision quantity used to quantify the severity of residual orthogonal mismatch in the target receiver during the initialization calibration period. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the orthogonal mismatch coefficient vector of the target receiver in the initial calibration period has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0079] Step A50: By multiplying the second loopback calibration signal with a complex exponential rotation factor generated by a preset frequency control word, the second loopback calibration signal is shifted to the zero-frequency baseband, thereby generating the third loopback calibration signal.

[0080] Understandably, shifting the second loopback calibration signal to the zero-frequency baseband results in a third loopback calibration signal in complex signal form that can be directly processed by the baseband, providing a unified baseband analysis benchmark for subsequent processing.

[0081] Step A60: The DC offset coefficient corresponding to the cascaded damage amount within the initial calibration cycle is superimposed on the third loopback calibration signal to obtain the fourth loopback calibration signal.

[0082] The formula for calculating the fourth loopback calibration signal is shown in Formula 20 below: Formula 20 in, This is the fourth loopback calibration signal. It's understandable that, compared to the third loopback calibration signal, the fourth loopback calibration signal also compensates for the DC offset damage in the cascaded damage during the initial calibration cycle. It is the third loopback calibration signal. , It is the DC offset coefficient corresponding to the cascaded damage amount within the initial calibration cycle.

[0083] In practical applications, to ensure that the DC offset coefficient of the cascaded channels can quickly approximate the actual damage value within the initial calibration period, an adaptive iterative algorithm can be used to update the DC offset coefficient of the cascaded channels in real time within the initial calibration period. The calculation method is shown in Formula 21 below: Formula 21 in, This represents the DC offset coefficient of the cascaded channels in the next initialization calibration cycle. This represents the iteration step size factor of the DC offset coefficient of the cascaded channels in the pre-set initialization calibration cycle. It is the fourth loop calibration signal, and at the same time, it serves as the error feedback quantity that drives the coefficient update during the initial calibration cycle.

[0084] Furthermore, when the DC offset coefficient of the initial calibration cycle cascaded channel gradually approaches the optimal value after multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the first-order statistics of the residual signal to calculate the fourth loop calibration signal. The normalized ratio of the arithmetic mean modulus to the average power over N sampling points is used as a measure of the residual DC offset of the cascaded channels during the initial calibration cycle.

[0085] First, calculate the ratio of the value of the fourth loopback calibration signal to the magnitude of the fourth loopback calibration signal to obtain the error feedback amount per unit amplitude of the fourth loopback calibration signal at one sampling point. Then, calculate the average value of the error feedback amount per unit amplitude at N sampling points during the initial calibration period to obtain the normalized statistical decision quantity (i.e., the first modulus of the arithmetic mean of the error feedback amount per unit amplitude of the fourth loopback calibration signal during the initial calibration period) used to quantify the severity of the residual DC bias in the cascaded channels during the initial calibration period. The calculation method of the normalized statistical decision quantity used to quantify the severity of the residual DC bias in the cascaded channels during the initial calibration period is shown in Formula 22 below: Formula 22 in, It is a normalized statistical decision quantity used to quantify the severity of residual DC bias in the cascaded channels during the initialization calibration cycle. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the DC offset coefficient of the cascaded channel in the initial calibration cycle has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0086] Step A70: Convert the fourth loopback calibration signal into a complex conjugate vector. Perform an inner product operation on the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount within the initial calibration period and the complex conjugate vector converted from the fourth loopback calibration signal. Then, superimpose the inner product operation result onto the fourth loopback calibration signal to obtain the fifth loopback calibration signal.

[0087] The calculation method for the fifth loop calibration signal is shown in Formula 23 below: Formula 23 in, This is the fifth loopback calibration signal. It can be understood that, compared to the fourth loopback calibration signal, the fifth loopback calibration signal has compensated for the orthogonal mismatch damage corresponding to the cascaded damage during the initial calibration cycle. It is the fourth loopback calibration signal. It is the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount within the initial calibration period. It is the complex conjugate vector converted from the fourth loop calibration signal.

[0088] In practical applications, to ensure that the orthogonal mismatch coefficient vector of the cascaded channels can quickly approximate the true damage value within the initial calibration cycle, an adaptive iterative algorithm can be used to update the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the current calibration cycle in real time. The calculation method is shown in Formula 24 below: Formula 24 in, This represents the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the next initialization calibration cycle. This represents the orthogonal mismatch coefficient vector corresponding to the cascaded damage during the initial calibration cycle. It is a preset iteration step size matrix that initializes the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the calibration cycle. It is used to control the speed and stability of the coefficient convergence along the gradient direction. It is the sequence of the fifth loop calibration signal. The fifth loop calibration signal obtained from Equation 23 is used as the error feedback quantity to drive coefficient updates during the initial calibration cycle.

[0089] Furthermore, when the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount of the initial calibration cycle gradually approaches the optimal value after multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the second-order statistics of the residual signal to calculate the fifth loop calibration signal. The normalized ratio of the conjugate second-order moment magnitude to the average power at N sampling points is used as a measure of the residual orthogonal mismatch of the cascaded channels during the initial calibration cycle.

[0090] First, calculate the ratio of the value of the fifth loop calibration signal to the magnitude of the fifth loop calibration signal to obtain the error feedback amount per unit amplitude of the fifth loop calibration signal at a sampling point. Then, calculate the average of the error feedback amounts per unit amplitude for N sampling points in the current sampling period to obtain the normalized statistical decision quantity (i.e., the first modulus of the arithmetic mean of the error feedback amounts per unit amplitude of the fifth loop calibration signal during the initial calibration period) used to quantify the severity of the residual orthogonal mismatch in the cascaded channels during the initial calibration period. The calculation method for the normalized statistical decision quantity used to quantify the severity of the residual orthogonal mismatch in the cascaded channels during the initial calibration period is shown in Formula 25 below: Formula 25 in, It is a normalized statistical decision metric used to quantify the severity of residual orthogonal mismatch in cascaded channels during initial calibration cycles. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the orthogonal mismatch coefficient vector of the cascaded channel in the initial calibration cycle has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0091] Step A80: The DC offset coefficient and quadrature mismatch coefficient vector of the target receiver for initializing the calibration period, and the DC offset coefficient and quadrature mismatch coefficient vector corresponding to the cascaded damage amount are used as the initialization calibration reference damage coefficient and / or the initialization calibration reference damage coefficient vector.

[0092] The initial calibration reference impairment coefficients refer to the combined DC offset coefficients of the target receiver and the cascaded channels, fixed after adaptive iterative convergence during the initial calibration phase. The initial calibration reference impairment coefficient vector refers to the combined orthogonal mismatch coefficient vectors of the target receiver and the cascaded channels, fixed after adaptive iterative convergence during the initial calibration phase.

[0093] The initialization calibration reference impairment coefficients and vector are only used in the fixed transmission error calibration phase. They serve as a known background reference for the complex DC signal in the loopback path, accurately stripping away fixed non-ideal characteristic impairments carried by the signal along the transmission path before pre-compensation in the cascaded channels. The fixed transmission error calibration phase refers to the process of calculating the fixed transmission error. In the actual calibration phase, the initialization calibration reference impairment coefficients and vector are not invoked; instead, all coefficients are cleared and adaptive iteration is restarted to track the time-varying impairments in real time. The actual calibration phase refers to the process of calibrating the transceiver signal during actual operation after completing the initial calibration and fixed transmission error calibration for the transceiver joint calibration.

[0094] This embodiment constructs a loopback path and injects a loopback calibration signal during the initialization calibration period. It then acquires a feedback signal, i.e., a loopback calibration response signal, which is superimposed with cascaded channel impairments and the target receiver's receive link impairments. After sequentially removing the target receiver's receive link impairments and cascaded channel impairments carried in the loopback calibration response signal, the adaptive iterative coefficients at each stage are solidified, resulting in the initialization calibration reference impairment coefficients and the initialization calibration reference impairment coefficient vector. This achieves decoupling of transmit / receive link impairments and fixed non-ideal characteristic impairments (i.e., fixed transmission errors) carried on the transmission path before cascaded channel pre-compensation, providing a reference for removing fixed transmission errors in the subsequent actual calibration stage.

[0095] Based on the second embodiment described above, a third embodiment of the transceiver joint calibration method of this application is proposed. Please refer to [link / reference]. Figure 3 Following step A80, steps A81 to A83 are also included: Step A81: Based on the loopback path, inject a complex DC signal into the target transmitter.

[0096] It is understandable that the spectrum of a complex DC signal is located at zero frequency, exhibiting a single frequency characteristic in the complex baseband. After the complex DC signal is transmitted through the converged and fixed correction links at each stage, the response of the transmission path before the pre-compensation of the cascaded channel to the complex DC signal degenerates into a fixed complex gain, i.e., a fixed transmission error. This fixed transmission error can be accurately isolated without being affected by frequency offset, image aliasing, or frequency selective fading.

[0097] Step A82: Based on the initialized calibration reference damage coefficient and / or the initialized calibration reference damage coefficient vector, compensate for the reference damage amount contained in the feedback signal of the complex DC signal to obtain the complex DC calibration signal of the complex DC signal.

[0098] The reference damage includes the receiver link damage and cascade damage during the initial calibration period, determined by the initial calibration reference damage coefficients and / or the initial calibration reference damage coefficient vector. By loading the initial calibration reference damage coefficients and / or the initial calibration reference damage coefficient vector, which are converged and solidified during the initialization phase, into the signal path, static compensation is performed on the known reference damage carried by the complex DC feedback signal. This removes the calibrated receiver link damage and cascade damage, resulting in a complex DC calibration signal containing only the fixed transmission error. This provides a clean observation sample after eliminating known damage for the calibration of the fixed transmission error, ensuring that the measurement of the fixed transmission error is not interfered with by the residual reference damage, and achieving accurate separation of the fixed transmission error and time-varying damage.

[0099] Understandably, based on the initial calibration reference impairment coefficient and / or initial calibration reference impairment coefficient vector corresponding to the target receiver, the DC offset impairment and quadrature mismatch impairment of the target receiver receiving link in the feedback signal of the complex DC signal are compensated. After frequency band shifting through a preset frequency control word, the DC offset impairment and quadrature mismatch impairment of the cascaded channel in the feedback signal of the complex DC signal are compensated based on the initial calibration reference impairment coefficient and / or initial calibration reference impairment coefficient vector corresponding to the cascaded channel. The resulting complex DC calibration signal contains only fixed transmission error.

[0100] Step A83: The ratio of the complex DC calibration signal to the complex DC signal is used as the fixed transmission error.

[0101] Fixed transfer error refers to the static complex gain introduced by the target transmitter, loopback path, target receiver, and receiver channel compensation stage along the transmission path of a complex DC signal from its injection into the baseband input port of the target transmitter, through the target transmitter, loopback path, target receiver, and receiver channel compensation stage, and finally from the output of the digital mixer (i.e., the transmission path before the signal enters the cascaded channel pre-compensation). It characterizes the inherent error carried by the signal at the initialization moment, before entering the cascaded channel pre-compensation. The value of the fixed transfer error remains unchanged when the hardware topology and initialization environment do not change substantially. It serves as a benchmark reference for removing inherent errors from the signal transmission path during the actual calibration stage. It is used to eliminate fixed non-ideal characteristic impairments carried by the signal on the transmission path before cascaded channel pre-compensation in the feedback loop, ensuring that the cascaded channel pre-compensation coefficients are iteratively updated only for time-varying cascaded impairments in the transmit link and spatial channel.

[0102] The calculation method for fixed transmission error is shown in Formula 26 below: Formula 26 Where G is the fixed propagation error. It is a complex DC calibration signal. It is a complex DC signal.

[0103] This embodiment injects a single-spectrum complex DC signal into the loopback path and uses the benchmark impairment coefficients that have converged during the initial calibration phase to statically compensate the feedback signal of the complex DC signal, thus removing known non-ideal characteristic impairments. This ensures that the complex DC calibration signal retains only the deterministic distortions carried on the transmission path before the pre-compensation of the cascaded channel. This guarantees that during the actual calibration phase, adaptive iteration only optimizes for time-varying transmit link and spatial channel impairments, thereby improving the accuracy and convergence efficiency of the entire link calibration.

[0104] Based on the first, second, and / or third embodiments described above, a fourth embodiment of the transceiver joint calibration method of this application is proposed. Please refer to [the relevant documentation]. Figure 4 Step S30 may include steps S311 to S314: Step S311: A cleaned observation signal that has been compensated for the fixed transmission error is generated by multiplying the second calibration signal and the reciprocal of the fixed transmission error.

[0105] The calculation method for purifying the observation signal is shown in Formula 27 below: Formula 27 in, It is to purify the observation signal. It is the second calibration signal. It is a fixed transmission error.

[0106] By multiplying the second calibration signal by the reciprocal of the fixed transmission error, fixed amplitude and phase distortions carried by the signal on the transmission path before pre-compensation in the cascaded channel are eliminated, generating a cleaned observation signal. The cleaned observation signal contains only cascaded impairment information of the transmit link and the space channel, serving as a pure error source for subsequent pre-compensation coefficient iterations. This ensures that the transmitter adaptive algorithm does not include the fixed transmission error in the compensation coefficients, thereby improving pre-distortion accuracy and convergence efficiency.

[0107] Step S312: Convert the purification observation signal into a complex conjugate vector, and perform an inner product operation on the orthogonal mismatch coefficient vector corresponding to the cascade damage amount and the complex conjugate vector converted from the purification observation signal to obtain the pre-compensation amount of orthogonal mismatch in the cascade channel.

[0108] After eliminating fixed transmission errors, the orthogonal mismatch pre-compensation amount generated through inner product operation is used only to offset time-varying image impairments in the transmit link and spatial channel. Since fixed transmission errors have been removed during the cleaned observation signal generation process, the pre-compensation amount obtained in this step does not include fixed transmission errors in the compensation coefficients. It is always optimized for time-varying cascaded channel impairments, ensuring that the transceiver joint calibration system uses its limited convergence degrees of freedom to fully address real channel variations, thereby achieving better performance in end-link image suppression and environmental adaptability.

[0109] Step S313: The pre-compensation amount is superimposed on the reference signal to be output to the target transmitter to obtain the reference signal with orthogonal mismatch pre-compensation.

[0110] The formula for calculating the reference signal after orthogonal mismatch pre-compensation is shown in Formula 28 below: Formula 28 in, The reference signal is pre-compensated for orthogonal mismatch. This is the reference signal to be output to the target transmitter. It is the pre-compensation amount for orthogonal mismatch in cascaded channels. It is the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount. It is to purify the observation signal. It is the complex conjugate vector converted from the purified observation signal.

[0111] It is understandable that the DC offset from the target receiver's receiving link has already been compensated before the purified observation signal undergoes spectrum shifting and compensation for fixed transmission errors. Therefore, the purified observation signal does not affect the orthogonal mismatch pre-compensation from the cascaded channel.

[0112] In practical applications, to ensure that the orthogonal mismatch coefficient vector of the cascaded channels can quickly approximate the true damage value, an adaptive iterative algorithm can be used to update the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the current calibration cycle in real time. The calculation method is shown in Formula 29 below: Formula 29 in, This represents the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the next calibration cycle. This represents the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount in the current calibration cycle. It is a preset iteration step size matrix for the orthogonal mismatch coefficient vector corresponding to the cascaded damage, used to control the speed and stability of coefficient convergence along the gradient direction. It is a sequence of purified observation signals for the current calibration cycle. The purified observation signal obtained from Formula 27 is used as the error feedback quantity to drive the coefficient update in the current calibration cycle.

[0113] Furthermore, when the orthogonal mismatch coefficient vector corresponding to the cascaded damage gradually approaches the optimal value after multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the second-order statistics of the residual signal to calculate the purified observation signal. The normalized ratio of the conjugate second-order moment magnitude to the average power at N sampling points is used as a measure of the residual orthogonal mismatch of the cascaded channels.

[0114] First, calculate the ratio of the purified observation signal value to the purified observation signal magnitude to obtain the error feedback amount per unit amplitude of the purified observation signal at one sampling point. Then, calculate the average of the squared error feedback amounts per unit amplitude of N sampling points in the current calibration period to obtain the normalized statistical decision quantity (i.e., the second modulus of the arithmetic mean of the squared error feedback amounts per unit amplitude of the purified observation signal in the current calibration period) used to quantify the severity of residual orthogonal mismatch in the cascaded channels. The calculation method of the normalized statistical decision quantity used to quantify the severity of residual orthogonal mismatch in the cascaded channels is shown in Formula 30 below: Formula 30 in, It is a normalized statistical decision metric used to quantify the severity of residual orthogonal mismatch in cascaded channels. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the orthogonal mismatch coefficient of the cascaded channel has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0115] Step S314: The DC offset coefficient corresponding to the cascaded damage is superimposed on the reference signal that has been pre-compensated for quadrature mismatch to obtain the full-link pre-calibration signal.

[0116] The calculation formula for the end-to-end pre-calibration signal is shown in Formula 31 below: Formula 31 in, It is a full-link pre-calibration signal. The reference signal obtained from Formula 28 after orthogonal mismatch pre-compensation is... It is the DC offset coefficient corresponding to the cascaded damage.

[0117] In practical applications, to ensure that the DC offset coefficient of the cascaded channel can quickly approximate the actual damage value, an adaptive iterative algorithm can be used to update the DC offset coefficient corresponding to the cascaded damage amount in the current calibration cycle in real time. The calculation method is as follows: Formula 32. Formula 32 in, This represents the DC offset coefficient of the cascaded channels in the next calibration cycle. The iteration step size factor represents the DC offset coefficient of the pre-set cascaded channels. The purified observation signal obtained from Formula 27 is used as the error feedback quantity to drive the coefficient update in the current calibration cycle.

[0118] Furthermore, when the DC offset coefficient of the cascaded channels gradually approaches the optimal value after multiple iterations, a convergence decision mechanism is needed to determine whether the iteration should stop. This implementation uses a normalized decision method based on the first-order statistics of the residual signal to calculate the purified observation signal. The normalized ratio of the arithmetic mean modulus to the average power at N sampling points is used as a measure of the residual DC offset of the cascaded channel.

[0119] First, calculate the ratio of the purified observation signal value to the purified observation signal magnitude to obtain the error feedback amount per unit amplitude of the purified observation signal at one sampling point. Then, calculate the average value of the error feedback amount per unit amplitude of the purified observation signal at N sampling points in the current calibration period to obtain the normalized statistical decision quantity (i.e., the first modulus of the arithmetic mean of the error feedback amount per unit amplitude of the purified observation signal in the current calibration period) used to quantify the severity of residual DC bias in the cascaded channel. The calculation method of the normalized statistical decision quantity used to quantify the severity of residual DC bias in the cascaded channel is shown in Formula 33 below: Formula 33 in, It is a normalized statistical decision quantity used to quantify the severity of residual DC bias in cascaded channels. The value of is directly used as one of the core criteria for determining whether the adaptive iteration has converged, where N is the total number of sampling points involved in the calculation. When When the value is below the preset threshold, it is determined that the DC offset coefficient of the cascaded channel has converged to the optimal value, the iteration is stopped and the current coefficient value is fixed.

[0120] This embodiment decouples the fixed transmission error from the feedback loop, ensuring that the pre-compensation amount is optimized only for time-varying transmit link and spatial channel impairments. This avoids the waste of convergence degrees of freedom caused by mistakenly including the fixed transmission error in the compensation coefficient, thereby improving the accuracy of full-link image suppression and the environmental tracking capability of the adaptive algorithm.

[0121] In one specific implementation, before obtaining the full-link pre-calibration signal, the fluctuation amplitude of environmental parameters (including but not limited to temperature, humidity, and power supply voltage) can be monitored in real time. When the environmental fluctuation exceeds a preset stability threshold, the environmental tracking mode of the transceiver joint calibration system is triggered. In environmental tracking mode, even if the first or second modulus value is lower than the preset convergence threshold, the iterative update of the calibration error value or calibration error value vector is maintained. At this time, the values ​​of each element in the iteration step size factor or iteration step size matrix are adjusted to a tracking step size value smaller than the normal convergence step size to reduce the over-adjustment sensitivity to residual errors, and the optimal compensation coefficient under the current environmental conditions is continuously iterated and tracked. When the environmental fluctuation is subsequently monitored to return to within the stability threshold, or the fluctuation of the iteratively updated calibration error value and calibration error value vector within N consecutive cycles is less than the preset stability threshold, it is determined that the current calibration error value or calibration error value vector has matched the link state after the environmental change, the iterative update is stopped, and the current calibration error value or calibration error value vector is used as the calibration error value or calibration error value vector for the current calibration cycle.

[0122] The tracking step size is typically smaller than the conventional convergence step size. Its specific value is determined by looking up a pre-defined mapping table between the tracking step size and environmental parameters, based on the sensor quantization value of the current environmental fluctuation amplitude. The environmental fluctuation amplitude can be provided by a temperature sensor, humidity sensor, or power supply voltage monitoring module.

[0123] As another feasible implementation of the environmental tracking mode, operators can determine whether the environment in which the target transmitter and receiver are located has changed significantly based on readings from external environmental monitoring instruments (such as thermometers, hygrometers, thermal imagers, or power ripple testers). If a large fluctuation in the environment is detected, the operator can manually trigger the transceiver joint calibration system to enter environmental tracking mode via a host computer or register configuration interface. The operator can then manually determine whether the current compensation coefficient has adapted to the link state after the environmental change based on the stable trend of the target transceiver's system performance indicators (such as EVM and image rejection ratio) observed in real time. If it is determined that it has adapted, the operator can freeze the current calibration error value or calibration error value vector via software commands, stop iterative updates, and save the current compensation coefficient as the optimal calibration result under the current environmental conditions.

[0124] The manual intervention mode and the aforementioned sensor-based automatic triggering environment tracking mode can coexist. When both modes are present, manual triggering has a higher priority than automatic triggering, in order to facilitate engineering debugging and forced intervention in abnormal scenarios.

[0125] The environmental tracking mode enables the transceiver joint calibration system to respond in real time to fluctuations in external environmental parameters such as temperature, humidity, and power supply voltage. After the normal convergence is completed, it continues to perceive and track the status of the transceiver link, which can ensure that the transceiver always operates in the optimal compensation state under different working environments.

[0126] For example, to help understand the implementation architecture of the transceiver joint calibration method formed by combining the above embodiments, please refer to... Figure 5 , Figure 6 , Figure 7 , Figure 8 , specifically: During the initial calibration phase, such as Figure 5 First, a loopback path is constructed between the target transmitter and the target receiver, and a loopback calibration signal o(n) is injected into the target transmitter. After the loopback calibration signal passes through the target transmitter, the loopback path, and the target receiver in sequence, a loopback calibration response signal is obtained. Then, by adjusting the loopback calibration response signal Perform receive channel compensation to obtain the second loopback calibration signal. Specifically, during the initial calibration cycle and the receive channel compensation phase, compensation for the loopback calibration response signal is also involved. The first loopback calibration signal obtained after the DC bias impairment of the target receiver carried during the initial calibration cycle. In the first loopback calibration signal Based on this, the quadrature mismatch loss of the target receiver during the initial calibration period is compensated to obtain the second loopback calibration signal. .

[0127] Then, the second loopback calibration signal is converted using a digital mixer. Complex exponential twitch factor generated by the preset frequency control word Perform complex multiplication to make the second loopback calibration signal Moved to zero-frequency baseband to generate a third loopback calibration signal .

[0128] Finally, the third loopback calibration signal Perform cascaded channel pre-compensation to obtain the fifth loopback calibration signal. In the initial calibration cycle and cascaded channel pre-compensation, the pre-compensation of the third loopback calibration signal is also involved. The fourth loopback calibration signal is obtained after the DC bias impairment of the cascaded channels carried during the initial calibration cycle. In the fourth loop back calibration signal Based on this, the orthogonal mismatch loss of the cascaded channels in the pre-compensation initialization calibration cycle is used to obtain the fifth loopback calibration signal. .

[0129] During the fixed transmission error calibration stage, such as Figure 6 First, based on the loopback path, a complex DC signal is injected into the target transmitter. Based on the initialization calibration reference damage coefficient and the initialization calibration reference damage coefficient vector fixed by the initialization calibration cycle, the complex DC signal is... Static compensation is performed on the feedback signal to compensate for the complex DC signal. Damage to the target receiver and cascaded channels resulted in a complex DC calibration signal. and the complex DC calibration signal With complex DC signal The ratio of is used as the fixed transmission error G.

[0130] In the actual calibration phase, such as Figure 7 , Figure 8 The loopback path is disconnected, and the signal of the transceiver is calibrated during actual operation. For signal X(n), the target calibration signal for the current calibration period is obtained after sequentially passing through the target transmitter, cascaded channel, and target receiver. First, the target calibration signal... Perform receive channel compensation to obtain the first calibration signal. In the actual calibration phase, the compensation of the receiving channel also involves compensating for the target calibration signal. The initial calibration signal obtained after the DC bias impairment of the target receiver carried in the current calibration period. In the initial calibration signal Based on this, the orthogonal mismatch loss of the target receiver in the current calibration cycle is compensated to obtain the first calibration signal. .

[0131] Then, the first calibration signal is converted using a digital mixer. Complex exponential twitch factor generated by the preset frequency control word Perform complex multiplication to make the first calibration signal Move to zero-frequency baseband to generate a second calibration signal .

[0132] Then, based on the fixed transmission error G calculated during the fixed transmission error calibration stage, the transmission path before removing the cascaded channel pre-compensation becomes the second calibration signal. Additional fixed transmission error, i.e., the second calibration signal Multiplying this by the reciprocal of the fixed propagation error G generates a cleaned observation signal that has been compensated for the fixed propagation error. .

[0133] Finally, the observation signal was purified. Perform cascaded channel pre-compensation to obtain end-to-end pre-calibration signal. In the actual calibration phase, the pre-compensation of the cascaded channels also involves obtaining the pre-compensation amount for orthogonal mismatch in the cascaded channels based on the purified observation signal, and then superimposing the pre-compensation amount onto the reference signal to be output to the target transmitter. The reference signal obtained after orthogonal mismatch pre-compensation is then obtained. and the reference signal after orthogonal mismatch pre-compensation Based on this, the DC offset coefficient corresponding to the cascaded damage is superimposed to obtain the full-link pre-calibration signal. .

[0134] To ensure that the calibration error values ​​and calibration error vectors in each stage of receiver channel compensation and cascaded channel pre-compensation can quickly approximate the true values, an adaptive iterative algorithm can be used to update each DC offset coefficient and orthogonal mismatch coefficient vector in real time. For each DC offset coefficient, a normalization decision method based on the first-order statistics of the residual signal can be used to determine whether the iteration should stop; for each orthogonal mismatch coefficient vector, a normalization decision method based on the second-order statistics of the residual signal can be used to determine whether the iteration should stop.

[0135] It should be noted that this example is only for the purpose of assisting in understanding this application and does not constitute a limitation on the transceiver joint calibration method of this application. Other technical solutions based on this concept are all within the protection scope of this application.

[0136] This application also provides a transceiver joint calibration device, which may include: at least one processor; and a memory communicatively connected to the at least one processor; wherein the memory stores instructions executable by the at least one processor, which are executed by the at least one processor to enable the at least one processor to perform the transceiver joint calibration method in the above embodiments.

[0137] The following is for reference. Figure 9 It shows a schematic diagram of the structure of a transceiver joint calibration device suitable for implementing the embodiments of this application. Figure 9 The transceiver joint calibration device shown is merely an example and should not impose any limitation on the functionality and scope of use of the embodiments of this application.

[0138] like Figure 9As shown, the transceiver joint calibration equipment may include a processing unit 101 (e.g., a central processing unit, a graphics processing unit, etc.), which can perform various appropriate actions and processes according to a program stored in read-only memory 102 or a program loaded from storage device 103 into random access memory 104. Random access memory 104 also stores various programs and data required for the operation of the transceiver joint calibration equipment. The processing unit 101, read-only memory 102, and random access memory 104 are interconnected via bus 105. Input / output interface 106 is also connected to bus 105. Typically, the following systems can be connected to input / output interface 106: input devices 107 including, for example, touch screens, touchpads, keyboards, mice, image sensors, microphones, accelerometers, gyroscopes, etc.; output devices 108 including, for example, liquid crystal displays (LCDs), speakers, vibrators, etc.; storage devices 103 including, for example, magnetic tapes, hard disks, etc.; and communication devices 109. Communication device 109 allows the transceiver joint calibration equipment to exchange data via wireless or wired communication with other devices. Although the diagram shows a transceiver joint calibration device with various systems, it should be understood that implementation or possession of all the systems shown is not required. More or fewer systems may be implemented alternatively.

[0139] In particular, according to embodiments of this disclosure, the processes described above with reference to the flowcharts can be implemented as computer software programs. For example, embodiments of this disclosure include a computer program product comprising a computer program carried on a computer-readable medium, the computer program containing program code for performing the methods shown in the flowcharts. In such embodiments, the computer program can be downloaded and installed from a network via a communication device, or installed from storage device 103, or installed from read-only memory 102. When the computer program is executed by processing device 101, it performs the functions defined in the methods of the embodiments of this application.

[0140] The transceiver joint calibration device provided in this application, employing the transceiver joint calibration method described in the above embodiments, can easily and efficiently achieve joint calibration of the receiver and transmitter. Compared with the prior art, the beneficial effects of the transceiver joint calibration device provided in this application are the same as those of the transceiver joint calibration method described in the above embodiments, and other technical features of the transceiver joint calibration device are the same as those disclosed in the methods of the above embodiments, and will not be repeated here.

[0141] It should be understood that various parts of the embodiments of this application can be implemented using hardware, software, firmware, or a combination thereof. In the description of the above embodiments, specific features, structures, materials, or characteristics can be combined in any suitable manner in one or more embodiments or examples.

[0142] The above description is merely a specific implementation of the embodiments of this application, but the protection scope of the embodiments of this application is not limited thereto. Any variations or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in this application should be included within the protection scope of the embodiments of this application. Therefore, the protection scope of the embodiments of this application should be determined by the protection scope of the above claims.

[0143] This application also provides a computer-readable storage medium storing a computer program that can run on a processor. The computer program is used to execute the transceiver joint calibration method in the above embodiments.

[0144] The computer-readable storage medium provided in this application embodiment may be, for example, a USB flash drive, but is not limited to, electrical, magnetic, optical, electromagnetic, infrared, or semiconductor systems or devices, or any combination thereof. More specific examples of computer-readable storage media may include, but are not limited to: electrical connections having one or more wires, portable computer disks, hard disks, random access memory (RAM), read-only memory (ROM), erasable programmable read-only memory (EPROM), optical fiber, portable compact disk read-only memory (CD-ROM), optical storage devices, magnetic storage devices, or any suitable combination thereof. In this embodiment, the computer-readable storage medium may be any tangible medium containing or storing a program that can be used by or in conjunction with an instruction execution system or device. The program code contained on the computer-readable storage medium may be transmitted using any suitable medium, including but not limited to: wires, optical cables, RF (Radio Frequency), etc., or any suitable combination thereof.

[0145] The aforementioned computer-readable storage medium may be included in the transceiver joint calibration equipment; or it may exist independently and not assembled into the transceiver joint calibration equipment.

[0146] The aforementioned computer-readable storage medium carries one or more programs. When these programs are executed by the transceiver joint calibration device, the transceiver joint calibration device: in the current calibration cycle, generates a first calibration signal by offsetting the receive link impairment in the target calibration signal output by the target receiver; shifts the first calibration signal to zero-frequency baseband by multiplying it by a complex exponential rotation factor generated by a preset frequency control word, generating a second calibration signal; the frequency control word is the difference between the local oscillator angular frequency of the target transmitter and the local oscillator angular frequency of the target receiver; extracts the cascade impairment carried in the second calibration signal, and couples the negative of the cascade impairment as a pre-compensation quantity into the reference signal to be output to the target transmitter, so as to achieve pre-calibration of the signal to be calibrated in the next calibration cycle in the current calibration cycle, obtaining a full-link pre-calibration signal; wherein, the cascade impairment includes the loss of the transmit link of the target transmitter and the loss of the cascaded channel formed by the spatial channel between the target transmitter and the target receiver.

[0147] Computer program code for performing the operations of this disclosure can be written in one or more programming languages ​​or a combination thereof, including object-oriented programming languages ​​such as Java, Smalltalk, and C++, and conventional procedural programming languages ​​such as the "C" language or similar programming languages. The program code can be executed entirely on the user's computer, partially on the user's computer, as a standalone software package, partially on the user's computer and partially on a remote computer, or entirely on a remote computer or server. In cases involving remote computers, the remote computer can be connected to the user's computer via any type of network—including a local area network (LAN) or a wide area network (WAN)—or can be connected to an external computer (e.g., via the Internet using an Internet service provider).

[0148] The flowcharts and block diagrams in the accompanying drawings illustrate the architecture, functionality, and operation of possible implementations of systems, methods, and computer program products according to various embodiments of this application. In this regard, each block in a flowchart or block diagram may represent a module, segment, or portion of code containing one or more executable instructions for implementing a specified logical function. It should also be noted that in some alternative implementations, the functions indicated in the blocks may occur in a different order than those indicated in the drawings. For example, two consecutively indicated blocks may actually be executed substantially in parallel, and they may sometimes be executed in reverse order, depending on the functions involved. It should also be noted that each block in the block diagrams and / or flowcharts, and combinations of blocks in the block diagrams and / or flowcharts, can be implemented using a dedicated hardware-based system that performs the specified function or operation, or using a combination of dedicated hardware and computer instructions.

[0149] The modules described in the embodiments of this application can be implemented in software or hardware. The names of the modules do not necessarily limit the functionality of the unit itself.

[0150] The computer-readable storage medium provided in this application embodiment stores computer-readable program instructions for executing the above-described transceiver joint calibration method, which can easily achieve efficient joint calibration of the receiver and transmitter. Compared with the prior art, the beneficial effects of the computer-readable storage medium provided in this application embodiment are the same as the beneficial effects of the transceiver joint calibration method provided in the above embodiments, and will not be repeated here.

[0151] This application also provides a computer program product, including a computer program that, when executed by a processor, implements the transceiver joint calibration method as described above.

[0152] The computer program product provided in this application embodiment can easily achieve efficient joint calibration of the receiver and transmitter. Compared with the prior art, the beneficial effects of the computer program product provided in this application embodiment are the same as those of the transceiver joint calibration method provided in the above embodiments, and will not be repeated here.

[0153] The above are merely preferred embodiments of this application and do not limit the patent scope of this application. Any equivalent structural or procedural transformations made using the content of this application's specification and drawings, or direct or indirect applications in other related technical fields, are similarly included within the patent protection scope of this application.

Claims

1. A transceiver joint calibration method, characterized in that, The method includes: In the current calibration cycle, a first calibration signal is generated by offsetting the receive link impairment in the target calibration signal output by the target receiver; By multiplying the first calibration signal by a complex exponential rotation factor generated by a preset frequency control word, the first calibration signal is shifted to the zero-frequency baseband, generating a second calibration signal; the frequency control word is the difference between the local oscillator frequency of the target transmitter and the local oscillator frequency of the target receiver. Extract the cascaded damage amount carried by the second calibration signal, and couple the inverse of the cascaded damage amount as a pre-compensation amount into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtain the full-link pre-calibration signal. The cascaded damage includes the loss of the transmission link of the target transmitter and the loss of the cascaded channel formed by the spatial channel between the target transmitter and the target receiver.

2. The method as described in claim 1, characterized in that, The step of generating a first calibration signal in the current calibration cycle by offsetting the receive link impairment in the target calibration signal output by the target receiver baseband analog front end includes: By superimposing the target calibration signal of the current calibration period with the DC offset coefficient of the target receiver of the current calibration period, an initial calibration signal that has compensated for the DC bias of the target receiver is obtained; The instantaneous compensation value for the orthogonal mismatch of the target receiver is obtained by performing an inner product operation on the target receiver orthogonal mismatch coefficient vector of the current calibration period and the complex conjugate vector of the initial calibration signal. The first calibration signal is obtained by superimposing the instantaneous compensation value onto the initial calibration signal.

3. The method as described in claim 1, characterized in that, The step of extracting the cascaded impairment amount carried by the second calibration signal and coupling the inverse of the cascaded impairment amount as a pre-compensation amount into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtaining the end-to-end pre-calibration signal, includes: The second calibration signal is converted into a complex conjugate vector, and the inner product operation is performed on the orthogonal mismatch coefficient vector corresponding to the cascaded damage amount and the complex conjugate vector converted from the second calibration signal to obtain the pre-compensation amount of orthogonal mismatch in the cascaded channel. The pre-compensation amount is superimposed on the reference signal to be output to the target transmitter to obtain the reference signal with orthogonal mismatch pre-compensation; The DC offset coefficient corresponding to the cascaded damage is superimposed on the reference signal that has undergone orthogonal mismatch pre-compensation to obtain the full-link pre-calibration signal.

4. The method as described in claim 1, characterized in that, The step of extracting the cascaded impairment amount carried by the second calibration signal and coupling the inverse of the cascaded impairment amount as a pre-compensation amount into the reference signal to be output to the target transmitter, so as to pre-calibrate the signal to be calibrated in the next calibration cycle in the current calibration cycle, and obtaining the end-to-end pre-calibration signal, includes: By multiplying the second calibration signal by the reciprocal of the fixed propagation error, a cleaned observation signal that has been compensated for the fixed propagation error is generated; The purification observation signal is converted into a complex conjugate vector, and the inner product operation is performed on the orthogonal mismatch coefficient vector corresponding to the cascade damage amount and the complex conjugate vector converted from the purification observation signal to obtain the pre-compensation amount of orthogonal mismatch in the cascade channel. The pre-compensation amount is superimposed on the reference signal to be output to the target transmitter to obtain the reference signal with orthogonal mismatch pre-compensation; The DC offset coefficient corresponding to the cascaded damage is superimposed on the reference signal that has undergone orthogonal mismatch pre-compensation to obtain the full-link pre-calibration signal.

5. The method as described in claim 4, characterized in that, The method further includes: During the initialization calibration period, a loopback path is constructed between the target transmitter and the target receiver, and a loopback calibration signal is injected into the target transmitter; After the loopback calibration signal passes sequentially through the target transmitter, the loopback path, and the target receiver, a loopback calibration response signal is obtained. The first loopback calibration signal is obtained by superimposing the loopback calibration response signal with the DC offset coefficient of the target receiver during the initial calibration period. The second loopback calibration signal is obtained by performing an inner product operation on the target receiver orthogonal mismatch coefficient vector of the initial calibration period and the complex conjugate vector of the first loopback calibration signal, and then superimposing the inner product operation result onto the first loopback calibration signal. By multiplying the second loopback calibration signal by a complex exponential rotation factor generated by the preset frequency control word, the second loopback calibration signal is shifted to the zero-frequency baseband, thereby generating a third loopback calibration signal. The DC offset coefficient corresponding to the cascaded damage amount within the initial calibration period is superimposed on the third loopback calibration signal to obtain the fourth loopback calibration signal; The fourth loopback calibration signal is converted into a complex conjugate vector. The orthogonal mismatch coefficient vector corresponding to the cascaded damage amount within the initial calibration period and the complex conjugate vector converted from the fourth loopback calibration signal are subjected to an inner product operation. The result of the inner product operation is superimposed on the fourth loopback calibration signal to obtain the fifth loopback calibration signal. The DC offset coefficient and quadrature mismatch coefficient vector of the target receiver during the initialization calibration period, and the DC offset coefficient and quadrature mismatch coefficient vector corresponding to the cascaded damage amount during the initialization calibration period are used as the initialization calibration reference damage coefficient and / or the initialization calibration reference damage coefficient vector.

6. The method as described in claim 5, characterized in that, After the step of using the DC offset coefficient and quadrature mismatch coefficient vector of the target receiver during the initialization calibration period, and the DC offset coefficient and quadrature mismatch coefficient vector corresponding to the cascaded impairment amount during the initialization calibration period as the initialization calibration reference impairment coefficient and / or the initialization calibration reference impairment coefficient vector, the following steps are included: Based on the loopback path, a complex DC signal is injected into the target transmitter; Based on the initial calibration reference impairment coefficient and / or the initial calibration reference impairment coefficient vector, the reference impairment amount contained in the feedback signal of the complex DC signal is compensated to obtain the complex DC calibration signal of the complex DC signal; the reference impairment amount includes the receive link impairment amount and the cascade impairment amount of the initial calibration period determined by the initial calibration reference impairment coefficient and / or the initial calibration reference impairment coefficient vector. The ratio of the complex DC calibration signal to the complex DC signal is used as the fixed transmission error.

7. The method according to any one of claims 1 to 6, characterized in that, The method further includes: In the current calibration cycle, the calibration error value and / or calibration error value vector corresponding to each iteration during the iterative calibration of the target calibration signal are obtained; Based on the calibration error value and / or calibration error value vector corresponding to each iteration, update the DC offset coefficient and / or orthogonal mismatch coefficient vector corresponding to the cascaded damage in the current calibration cycle; And / or, based on the calibration error value and / or calibration error value vector corresponding to each iteration, update the DC offset coefficient and / or quadrature mismatch coefficient vector of the target receiver in the current calibration cycle.

8. The method as described in claim 7, characterized in that, The method further includes: Divide the value of each error feedback quantity by its respective modulus to obtain the error feedback quantity per unit amplitude. For any of the error feedback quantities, if the data type of the error feedback quantity is the signal value of the signal after compensation or pre-compensation of DC bias, then the first modulus value of the arithmetic mean of the error feedback quantity per unit amplitude is calculated. If the data type of the error feedback quantity is the signal value of the signal after compensation or pre-compensation orthogonal mismatch, calculate the second modulus value of the arithmetic mean of the square of the error feedback quantity per unit amplitude; When the first modulus or the second modulus is lower than the preset convergence threshold, the calibration error value and / or calibration error value vector corresponding to the error feedback quantity is used as the calibration error value and / or calibration error value vector at the next moment.

9. A transceiver joint calibration device, characterized in that, The transceiver joint calibration device includes: a memory, a processor, and a computer program stored in the memory and executable on the processor, the computer program being configured to implement the transceiver joint calibration method as described in any one of claims 1 to 8.

10. A computer-readable storage medium, characterized in that, The computer-readable storage medium stores a computer program that, when executed by a processor, implements the transceiver joint calibration method as described in any one of claims 1 to 8.

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