Magnetic component and electric / electronic device

Abstract

The magnetic component 1 according to one aspect of the present application includes a magnetic core 10 having at least one set of opposing leg portions (middle leg portions 12) and forming a first gap L1 with the set of leg portions (middle leg portions 12), and a winding 20 wound around the set of leg portions (middle leg portions 12) in a direction in which the set of leg portions (middle leg portions 12) extends and wound in multiple layers in a manner of overlapping in a direction substantially perpendicular to the direction of extension. Since the winding 20 is composed of a plurality of magnetic plated litz wires in which a plurality of single wires are bundled, at least in a region surrounding the first gap L1, and the frequency of the driving condition is 200 kHz or more, copper loss at high frequencies can be sufficiently suppressed even in the case where the magnetic plated litz wire is wound around the magnetic core provided with the gap.

Description

Technical Field

[0001] This invention relates to magnetic components and electrical / electronic machines. Background Technology

[0002] Patent Document 1 discloses a reactor capable of simultaneously reducing winding eddy current losses caused by leakage flux from the core gap and reducing winding resistance. The reactor has at least one set of opposing legs, a core with a gap formed by the aforementioned set of legs, and a winding wound in multiple layers along the extension direction of the aforementioned set of legs and overlapping in a direction substantially perpendicular to the extension direction. In the region surrounding the gap, the innermost periphery of the winding is composed of Litz wire formed by multiple strands twisted together, and the outermost periphery of the winding is composed of a single wire.

[0003] Patent Document 2 discloses a conductor capable of reducing losses in DC-DC superimposed high-frequency circuits, low-frequency superimposed high-frequency circuits, or high-frequency circuits with frequency variations. This conductor is characterized by forming a magnetic plating layer on the surface of a copper wire, and forming an insulating coating on the surface of this magnetic plating layer, and then stranding or unstretching multiple copper wires with this insulating coating and magnetic material plating together.

[0004] [Existing Technical Documents] [Patent Literature] [Patent Document 1] International Publication No. 2012 / 017616 [Patent Document 2] Japanese Patent Application Publication No. 2009-277396 Summary of the Invention

[0005] [The technical problem that the invention aims to solve] When magnetic components are used in high-frequency circuits, losses tend to increase due to the AC resistance present in the wound magnetic components. Specifically, two factors contribute to AC resistance in the windings: the skin effect and the proximity effect. As a countermeasure to the skin effect, a common practice is to divide the conductor into multiple strands to reduce the cross-sectional area of ​​each individual conductor and to use Litz wire bundled together. However, as the number of bundled conductors increases, the proximity effect intensifies, thus limiting the reduction of AC resistance.

[0006] As a means to address this "proximity effect," one example is the use of magnetically plated Litz wire. In magnetically plated Litz wire, the magnetic field generated by the current flowing through one magnetically plated copper wire is blocked by the magnetic material coating, making it difficult for it to enter the copper wire portion of other magnetically plated copper wires. Therefore, it is desirable to suppress the increase in copper loss caused by the proximity effect.

[0007] Here, gaps are incorporated into the magnetic core to control magnetic saturation. Even when magnetically coated Litz wire is wound on a core with such gaps and driven at high frequencies, it is still desirable to sufficiently suppress copper losses.

[0008] The purpose of this invention is to provide a magnetic component and an electrical / electronic device that can sufficiently suppress copper loss at high frequencies even when a magnetically coated Litz wire is wound on a magnetic core with gaps.

[0009] [Technical solution to the problem] A magnetic component according to one aspect of the present invention comprises: a magnetic core having at least one set of opposing legs forming a first gap L1; and a winding wound around the set of legs along the extending direction of the set of legs, and wound in multiple layers in an overlapping manner in a direction substantially perpendicular to the extending direction; characterized in that, at least in the region surrounding the first gap L1, the winding is composed of a plurality of magnetically plated Litz wires made of single wire bundles, and the frequency of the driving condition is 200 kHz or higher.

[0010] According to this structure, by winding multiple single-strand magnetic coated Litz wires in the magnetic core at least around the region of the first gap, and setting the frequency of the driving condition to 200kHz or above, it is possible to reduce the eddy current loss in the winding caused by the leakage flux of the first gap of the magnetic core.

[0011] The aforementioned magnetic component includes a coil comprising a winding wound around the aforementioned set of feet. A second gap L2 is provided and configured between the coil and the aforementioned set of feet. Preferably, the second gap L2 and the first gap L1 satisfy L2. 2 / L1≤1.6. The larger the first gap L1 is, the greater the leakage flux, and thus the copper loss is more likely to increase, which makes the effect of using magnetically plated Litz wire more apparent.

[0012] In the aforementioned magnetic components, the winding can also be composed of the aforementioned magnetically coated Litz wire and single wire or Litz wire. In the portion farther from the first gap, it is less susceptible to the increased losses caused by leakage flux. By using single wire or Litz wire to construct the portion less affected by this effect, costs can be reduced.

[0013] In the aforementioned magnetic component, when the distance between the winding and the first gap L1 is set to Ds, the winding located at Ds... 2The near-position windings within the range of / L1≤1.6 preferably include a portion composed of the aforementioned magnetically coated Litz wire. If the spacing distance Ds is short, it is susceptible to increased losses due to leakage flux from the first gap. Therefore, by using magnetically coated Litz wire in the windings within this range, losses can be suppressed and costs can be reduced.

[0014] In the aforementioned magnetic components, the outer diameter of the aforementioned magnetically coated Litz wire or the outer diameter of the aforementioned Litz wire can differ from the outer diameter of the aforementioned single wire. By changing the outer diameter of the wire in conjunction with the current conditions of the circuit, miniaturization and cost reduction can be achieved. Especially in the case of a single wire, compared with Litz wire, even with the same final cross-sectional area, the increased cross-sectional area of ​​the conductor itself provides the advantage of reduced DC resistance.

[0015] Another aspect of the invention is an electrical / electronic machine incorporating the aforementioned magnetic components. According to this structure, low loss and high efficiency can be achieved while employing a ferrite core with a gap.

[0016] [The effects of the invention] According to the present invention, a magnetic component and an electrical / electronic device are provided that can sufficiently suppress copper loss at high frequencies even when a magnetically coated Litz wire is wound on a magnetic core with gaps. Attached Figure Description

[0017] Figure 1 An example perspective view of the magnetic component in this embodiment is shown.

[0018] Figure 2 A cross-sectional view of the magnetic component in this embodiment is shown.

[0019] Figure 3A This is a top view of the magnetic core.

[0020] Figure 3B This is a front view of the magnetic core.

[0021] Figure 4 The graph shows the loss of components 1A and 1B relative to the magnetic flux density at a driving frequency of 100kHz.

[0022] Figure 5 The graph shows the loss of components 1A and 1B relative to the magnetic flux density at a driving frequency of 250kHz.

[0023] Figure 6 The graph shows the loss of components 1A and 1B relative to the magnetic flux density at a driving frequency of 500kHz.

[0024] Figure 7The graph shows the loss of components 1A and 1B relative to the magnetic flux density at a driving frequency of 1MHz.

[0025] Figure 8 The graph shows the loss of components 2A and 2B relative to the magnetic flux density at a driving frequency of 100kHz.

[0026] Figure 9 The graph shows the loss of components 2A and 2B relative to the magnetic flux density at a driving frequency of 250kHz.

[0027] Figure 10 The graph shows the loss of components 2A and 2B relative to the magnetic flux density at a driving frequency of 500kHz.

[0028] Figure 11 The graph shows the loss of components 2A and 2B relative to the magnetic flux density at a driving frequency of 1MHz.

[0029] Figure 12 The graph shows the loss of verification components 1A and 1B relative to the driving frequency.

[0030] Figure 13 A graph showing the loss ratio relative to the driving frequency.

[0031] Figure 14 This indicates that at a driving frequency of 250kHz, relative to L2 2 A diagram of copper loss at / L1.

[0032] Figure 15 This indicates that at a driving frequency of 500kHz, relative to L2 2 A diagram of copper loss at / L1. Detailed Implementation

[0033] Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings. Furthermore, in the following description, the same reference numerals are used for the same components, and descriptions of components already described are omitted where appropriate.

[0034] (Magnetic components) Figure 1 This is a perspective view illustrating the appearance of the magnetic component according to this embodiment.

[0035] Figure 2 This is a cross-sectional view illustrating the magnetic component of this embodiment. Figure 2 It shows Figure 1 A sectional view along line A-A'.

[0036] Figure 3A This is a top view of the magnetic core.

[0037] Figure 3B This is a front view of the magnetic core.

[0038] The magnetic component 1 of this embodiment includes: a magnetic core 10 having at least one set of opposing legs; and a winding 20 wound around the set of legs along the extending direction of the aforementioned set of legs. In this embodiment, the extending direction of the set of legs is defined as the X direction (length direction), one of the directions orthogonal to the X direction is defined as the Y direction (width direction), and the direction orthogonal to both the X and Y directions is defined as the Z direction (thickness direction). The magnetic core 10, for example, has a pair of magnetic cores 11. Each magnetic core 11 has: a central leg 12, side legs 13 disposed on both sides of the central leg 12, and a connecting portion 14 connecting the central leg 12 and the side legs 13. The magnetic core 11 has a generally E-shaped form due to the central leg 12, the side legs 13, and the connecting portion 14, and the tips of the side legs 13 of the pair of magnetic cores 11 abut against each other in the X direction. Furthermore, a first gap L1 (hereinafter also simply referred to as "L1") is provided between the central legs 12 of the abutted pair of magnetic cores 11 in the X direction.

[0039] The magnetic material of the magnetic core 10 is made of ferrite. Since ferrite is a material that can handle complex shapes, the production efficiency of the magnetic core can be improved by using ferrite as the material for magnetic core 11, which has a complex shape such as a roughly E-shape.

[0040] The size of the magnetic core 10 is appropriately selected according to the specifications of the magnetic component 1. For example, Figure 3B The thickness T shown is approximately 5.0 mm. Figure 3A The width W shown is approximately 19.3 mm, the length L is approximately 15.8 mm, the length Ls of the side foot 13 is approximately 5.8 mm, the width Wc of the middle foot 12 is approximately 4.0 mm, and the inner distance Wi between the left and right side feet 13 is approximately 15.1 mm.

[0041] The winding 20 is wound on the middle leg 12 along the extending direction of the middle leg 12, and is wound in multiple layers in a manner that overlaps in a direction substantially perpendicular to the extending direction. The winding 20 may also be wound on a winding frame 30 provided around the middle leg 12.

[0042] As an example, in this embodiment, a primary winding 21 and a secondary winding 22 are wound on the winding frame 30. The primary winding 21 is wound inside and outside the secondary winding 22. That is, the winding 20 has a sandwich winding structure in which the secondary winding 22 is sandwiched in the middle by the primary winding 21 on the inner and outer sides. A signal detection line 25 for control can also be wound on the winding frame 30.

[0043] In the magnetic component 1 with such a structure, at least in the region surrounding the first gap L1, the winding 20 is composed of multiple bundles of magnetically plated Litz wire, and the circuit driving condition using the magnetic component 1 is a frequency of 200 kHz or higher. The magnetically plated Litz wire is a wire formed by stranding or unstretching multiple copper wires coated with insulating magnetic material. This insulating coating is obtained by forming a magnetic material coating on the surface of a conductor, such as copper wire, and then forming an insulating coating on the surface of this magnetic material coating. By winding the magnetically plated Litz wire in the magnetic core 10 at least around the region of the first gap L1 and setting the driving frequency to 200 kHz or higher, the eddy current losses in the winding 20 caused by the leakage flux of the first gap L1 of the magnetic core 10 can be reduced.

[0044] Additionally, the magnetic component 1 includes a coil (e.g., a primary winding 21 and a secondary winding 22) comprising a winding 20 wound around the middle foot 12 (a set of feet). A second gap L2 (hereinafter also simply referred to as "L2") is provided between the coil and the middle foot 12 (a set of feet). Here, in the magnetic component 1, the second gap L2 and the first gap L1 satisfy L2. 2 The structure is defined as L1 ≤ 1.6. A larger first gap L1 results in increased leakage flux and a greater likelihood of increased copper loss, thus making the effect of using magnetically plated Litz wire more apparent. Therefore, by setting it to satisfy L2... 2 The structure with / L1≤1.6 can reduce the eddy current loss in winding 20 caused by the leakage flux of the first gap L1.

[0045] Furthermore, when a magnetically coated Litz wire is wound as a winding 20 around at least the region surrounding the first gap L1 in the magnetic core 10, such as Figure 2 As shown, if the interval distance between the winding and the first gap L1 (the radius of the circle centered on the intersection of the Z-direction line passing through the center of the first gap L1 and the extended surface of the outer periphery of the middle leg 12) is set as Ds, then the winding located at Ds in the aforementioned winding... 2 The near-position windings within the range of / L1≤1.6 preferably include a portion composed of magnetically plated Litz wire. If the spacing distance Ds is short, it is susceptible to increased losses due to leakage flux from the first gap L1. Therefore, by using magnetically plated Litz wire in the windings 20 within at least this range, it is possible to simultaneously suppress losses and reduce costs.

[0046] Here, the winding 20 can be entirely made of magnetically plated Litz wire, or a portion of the winding 20 can be made of magnetically plated Litz wire, while another portion can be made of single wire or Litz wire. In the portion farther from the first gap L1, the increased losses due to leakage flux are less likely to occur; therefore, by using single wire or Litz wire to construct these less affected portions, costs can be reduced.

[0047] Furthermore, when the winding 20 is constructed from magnetically plated Litz wire and a single wire or a combination of Litz wires, the outer diameter of the magnetically plated Litz wire or the outer diameter of the Litz wire can differ from the outer diameter of the single wire. By changing the outer diameter of the wire according to the current conditions of the circuit, miniaturization and cost reduction can be achieved. Especially in the case of a single wire, compared to Litz wire, even with the same final cross-sectional area, the increased cross-sectional area of ​​the conductor itself provides the benefit of reduced DC resistance.

[0048] (Verification results) Next, the verification results of the magnetic component 1 of this embodiment will be explained. Here, the verification results of a magnetic component (referred to as verification component 1A) as one embodiment of the magnetic component 1 of this embodiment and magnetic components (referred to as verification components 1B, 2A, 2B) with structures different from verification component 1A are shown.

[0049] [Structure of Verification Component 1A] The material of the magnetic core 10 of the verification component 1A is Mn-Zn ferrite. The shape of the pair of magnetic cores 11 is as follows: Figure 3A and Figure 3B The magnetic core 10 is roughly E-shaped. Its dimensions are: thickness T approximately 5.0 mm, width W approximately 19.3 mm, length L approximately 15.8 mm, length Ls of side legs 13 approximately 5.8 mm, width Wc of middle leg 12 approximately 4.0 mm, and inner spacing Wi between the left and right side legs 13 approximately 15.1 mm. The effective cross-sectional area of ​​the magnetic core 10 is 20.65 mm². 2 The effective magnetic circuit length of magnetic core 10 is 39.15 mm. The length of the first gap L1 is 0.8 mm, and the length of the second gap L2 is 0.85 mm ± 0.1 mm. The primary winding 21 in the winding (equivalent to winding 20, the same below) consists of 13 diameter... Magnetic-coated Litz wire (0.102 mm² cross-sectional area) made of stranded 0.1 mm thick conductors. 2 The secondary winding 22 is composed of 70 diameter wires. Magnetic-coated Litz wire (cross-sectional area 0.550 mm²) is made by twisting together 0.1 mm thick conductors. 2 The primary winding 21 has 32 turns, and the secondary winding 22 has 4 turns. The DC resistance of the primary winding 21 at 20°C is 175mΩ, and the DC resistance of the secondary winding 22 at 20°C is 13.2mΩ. The primary-side inductance is 50.2μH at 100MHz, and the leakage inductance is 7.53μH at 100kHz (secondary winding short-circuited).

[0050] [Structure of Verification Component 1B] The structure of verification component 1B is identical to that of verification component 1A, except for the windings. The windings of verification component 1B are made of Litz wire (Litz wire without magnetic plating). Furthermore, the conductor specifications, number of bundled strands, and number of turns of the Litz wire used in the windings of verification component 1B are the same as those of the magnetically plated Litz wire used in the windings of verification component 1A. In verification component 1B, which uses Litz wire in its windings, the DC resistance of the primary winding at 20°C is 179 mΩ, and the DC resistance of the secondary winding at 20°C is 12.8 mΩ. The primary-side inductance is 49.5 μH at 100 MHz, and the leakage inductance is 6.44 μH at 100 kHz (secondary winding short-circuited).

[0051] [Structure of Verification Component 2A] The magnetic core of verification component 2A is made of soft magnetic metal material through powder pressing. The shape of a pair of magnetic cores is... Figure 3A and Figure 3B The magnetic core is roughly E-shaped. Its dimensions are: thickness T approximately 7.0 mm, width W approximately 19.3 mm, length L approximately 15.8 mm, length Ls of side legs 13 approximately 5.8 mm, width Wc of center leg 12 approximately 4.0 mm, and inner spacing Wi between the left and right side legs 13 approximately 15.1 mm. The effective cross-sectional area of ​​the magnetic core is 28.90 mm². 2 The effective magnetic path length of the magnetic core is 39.15 mm. The length of the first gap L1 is zero (0, no gap), and the length of the second gap L2 is 0.85 mm ± 0.1 mm. The winding structure (wire specifications, number of bundles, and number of turns) of verification component 2A is the same as that of verification component 1A. The DC resistance of the primary winding at 20°C is 198 mΩ, and the DC resistance of the secondary winding at 20°C is 13.8 mΩ. The primary-side inductance is 55.1 μH at 100 MHz, and the leakage inductance is 7.80 μH at 100 kHz (secondary winding short-circuited).

[0052] [Verification of the structure of component 2B] The structure of verification component 2B is identical to that of verification component 2A, except for the windings. The windings of verification component 2B are made of Litz wire (Litz wire without magnetic plating). Furthermore, the conductor specifications, number of bundled strands, and number of turns of the Litz wire used in the windings of verification component 2B are the same as those of the magnetically plated Litz wire used in the windings of verification component 2A. In verification component 2B, which uses Litz wire in its windings, the DC resistance of the primary winding at 20°C is 206 mΩ, and the DC resistance of the secondary winding at 20°C is 14.7 mΩ. The primary-side inductance is 54.5 μH at 100 MHz, and the leakage inductance is 7.79 μH at 100 kHz (secondary winding short-circuited).

[0053] [Loss relative to magnetic flux density] Figures 4 to 7 This is a graph showing the loss of verification components 1A and 1B relative to the magnetic flux density.

[0054] Figure 4 This indicates the case where the driving frequency is 100kHz. Figure 5 This indicates the case where the driving frequency is 250kHz. Figure 6 This indicates the case where the driving frequency is 500kHz. Figure 7 This indicates the case where the driving frequency is 1MHz. Furthermore, Tables 1 to 4 show... Figures 4 to 7 The loss value is shown relative to the magnetic flux density (Bm).

[0055] [Table 1] Drive frequency 100kHz

[0056] [Table 2] Drive frequency 250kHz

[0057] [Table 3] Drive frequency 500kHz

[0058] [Table 4] Drive frequency 1 MHz

[0059] Although both verification components 1A and 1B have a first gap L1 in their magnetic cores, the winding of verification component 1A is a magnetically coated Litz wire, while the winding of verification component 1B is an uncoated Litz wire. For example... Figures 4 to 7 As shown, at lower driving frequencies, the loss difference between verification component 1A and verification component 1B is not significant. However, as the driving frequency increases, the loss of verification component 1A becomes smaller than that of verification component 1B. Therefore, it can be said that with the first gap L1 provided in the magnetic core, the higher the driving frequency, the more significant the effect (loss reduction) of using magnetically plated Litz wire for winding.

[0060] Figures 8 to 11 This is a graph showing the loss of verification components 2A and 2B relative to the magnetic flux density.

[0061] Figure 8 This indicates the case where the driving frequency is 100kHz. Figure 9 This indicates the case where the driving frequency is 250kHz. Figure 10 This indicates the case where the driving frequency is 500kHz. Figure 11This indicates the case where the driving frequency is 1MHz. Furthermore, Tables 5 to 8 show... Figures 8 to 11 The loss value is shown relative to the magnetic flux density (Bm).

[0062] [Table 5] Drive frequency 100kHz

[0063] [Table 6] Drive frequency 250kHz

[0064] [Table 7] Drive frequency 500kHz

[0065] [Table 8] Drive frequency 1 MHz

[0066] Neither of the magnetic cores of verification components 2A nor 2B contains a first gap L1. The winding of verification component 2A is a magnetically coated Litz wire, while the winding of verification component 2B is an uncoated Litz wire. Figures 8 to 11 As shown, in verification components 2A and 2B, the difference in losses due to the different driving frequencies is not significant. Therefore, it can be said that without the first gap L1 in the magnetic core, the effect (loss reduction) of using magnetically coated Litz wire for the winding is difficult to demonstrate.

[0067] [Loss relative to drive frequency] Figure 12 This is a graph showing the loss of verification components 1A and 1B relative to the driving frequency.

[0068] Figure 12 It shows Figures 4 to 7 The loss relative to the driving frequency is shown when the magnetic flux density is 10 mT. Furthermore, Table 9 shows... Figure 12 The loss value relative to the driving frequency is shown.

[0069] [Table 9] 10 mT loss [W]

[0070] like Figure 12As shown, when a first gap L1 is provided on the magnetic core, the loss of verification component 1B is slightly lower than that of verification component 1A at a driving frequency of 100kHz. On the other hand, when the driving frequency exceeds 170kHz, the loss of verification component 1A is lower than that of verification component 1B, and this difference becomes significant at 200kHz or above.

[0071] Figure 13 This is a graph showing the loss ratio of the magnetic coating Litz lines (verification components 1A, 2A) and Litz lines (verification components 1B, 2B) relative to the driving frequency.

[0072] exist Figure 13 In, it is shown Figures 4 to 11 The diagram shows the relationship between the driving frequency (horizontal axis) and the loss ratio (vertical axis) of components 1A, 1B, 2A, and 2B under a magnetic flux density of 10 mT. Here, the loss ratio is the ratio of the loss of the magnetic coating Litz wire to the loss of the Litz wire itself. Figure 13 The table shows the ratio of the loss of verification component 1A to the loss of verification component 1B, and the ratio of the loss of verification component 2A to the loss of verification component 2B. The loss values ​​of verification components 1A and 1B are shown in Table 9. The losses and loss ratios of verification components 2A and 2B are shown in Table 10.

[0073] [Table 10] 10 mT loss [W]

[0074] like Figure 13 As shown, in the verification components 2A and 2B without the first gap L1 in the magnetic core, the loss ratio hardly changes with the driving frequency. On the other hand, in the verification components 1A and 1B with the first gap L1 in the magnetic core, the loss ratio is higher than that of verification components 2A and 2B at a driving frequency of 100kHz, but lower at a driving frequency of 200kHz or higher.

[0075] Therefore, it can be seen that when the magnetic core is provided with a first gap L1 and magnetically coated Litz wire is used as the winding, by making the driving frequency 200kHz or above, the eddy current loss in the winding caused by the leakage flux of the first gap L1 of the magnetic core can be effectively reduced.

[0076] [L1 and L2] 2 [Relationship between them] Figure 14 and Figure 15 It means relative to L2 2 A diagram of copper loss at / L1.

[0077] The specifications of the magnetic components used in the verification are as follows: Core size: PQ20 / 16Z-12 (manufactured by TDK, PQ series ferrite core for switching power supplies) Core material: Ferrite Winding specifications: 20 wires with a diameter of Litz wire, made of stranded 0.1mm conductors. Number of winding turns: 30 turns Inductance: 154μH Applied current: Sine wave (peak current 2A) Figure 14 This indicates that the driving frequency is 250kHz. Figure 15 This indicates that at a driving frequency of 500kHz, each is relative to L2. 2 / L1 copper loss.

[0078] In addition, Table 11 shows Figure 14 The figure shown is relative to L2 2 The copper loss values ​​for / L1 are shown in Table 12. Figure 15 The figure shown is relative to L2 2 The copper loss value of / L1. As shown in Tables 11 and 12, in this verification, multiple magnetic components were prepared with the first gap L1 fixed and the second gap L2 changed, and the copper loss of these magnetic components was measured.

[0079] [Table 11]

[0080] [Table 12]

[0081] The larger the first gap L1, the greater the leakage flux; conversely, the smaller the second gap L2 (i.e., the closer the coil is to the first gap L1), the more susceptible it is to the leakage flux from the first gap L1, thus increasing copper losses. Figure 14 and Figure 15 As shown, in L2 2 A significant increase in copper loss can be observed when L1 is below 1.6. Therefore, it can be concluded that by satisfying L2... 2 Using magnetically plated Litz wire within the range of / L1≤1.6 can reduce winding eddy current losses caused by leakage flux of the first gap L1.

[0082] On the other hand, satisfying L2 2Within the range of / L1>1.6, due to the lower copper loss, for example in areas where the distance from the first gap L1 exceeds a certain distance, ordinary Litz wire or single wire that is not magnetically plated Litz wire can also be used.

[0083] Furthermore, it is even more preferable to use as Figure 2 The interval distance Ds shown, when satisfying Ds 2 The range where L1 ≤ 1.6, i.e., where Ds ≤ (1.6 × L1). 1 / 2 The near-field winding includes a portion composed of magnetically plated Litz wire. This satisfies Ds ≤ (1.6 × L1). 1 / 2 The range is particularly susceptible to the leakage flux from the first gap L1. Therefore, by including magnetically plated Litz wire in the coil structure within this range, the winding eddy current losses caused by the leakage flux from the first gap L1 can be effectively reduced.

[0084] Furthermore, given that Ds > (1.6 × L1) 1 / 2 Within this range, since the benefits of using magnetically coated Litz wire are relatively small, it is possible to reduce costs while suppressing losses by using ordinary Litz wire or single wire within this range.

[0085] Based on the above verification results, the following can be concluded: (1) In the magnetic components used in magnetic cores without gaps in the magnetic circuit, the loss difference between magnetically coated Litz wires and uncoated Litz wires is slight.

[0086] (2) In magnetic components such as ferrite cores, where gaps are provided in the magnetic circuit, the loss difference between magnetically coated Litz lines and uncoated Litz lines occurs when the driving frequency is 200 kHz or higher, and the magnetically coated Litz lines tend to have smaller losses.

[0087] (3) When the driving frequency is below 200kHz, the loss difference reverses. Compared with the magnetically coated Litz line, the uncoated Litz line shows a trend of lower loss.

[0088] The results above show that the effect of using magnetically plated Litz wire to suppress proximity effects is minimal in magnetic components such as transformers where the wire is wound around an iron core. However, the magnetically plated Litz wire is more effective in suppressing the eddy current effects caused by leakage flux through the wire due to gaps in the iron core. Furthermore, this effect is observed when the driving frequency of the circuit is set to 200kHz or higher; conversely, the losses increase as the driving frequency decreases.

[0089] Based on the verification results, it can be concluded that by having a magnetic component 1 that satisfies the two conditions that the winding 20 in the magnetic core 10 is made of magnetically plated Litz wire at least in the region surrounding the first gap L1 and that the driving frequency is 200 kHz or above, the eddy current loss in the winding 20 caused by the leakage flux of the first gap L1 can be reduced.

[0090] (Electrical / Electronic Machinery) An electrical / electronic device according to one embodiment of the present invention is equipped with the magnetic component 1 described in the above embodiment. Examples of such electrical / electronic devices include power supply devices with switching power supply circuits, buck-boost circuits, smoothing circuits, etc., and small portable communication devices. Since the magnetic component 1 of this embodiment can achieve low loss in the high-frequency region with a driving frequency of 200 kHz or higher, it is easy to miniaturize the electrical / electronic device equipped with this magnetic component 1.

[0091] In summary, according to this embodiment, a magnetic component 1 and an electrical / electronic device can be provided that can sufficiently suppress copper loss at high frequencies even when a magnetically plated Litz wire is wound on a magnetic core with gaps.

[0092] Furthermore, although the embodiments described above are specific to this invention, the invention is not limited to these examples. For instance, the shape of the magnetic core 10 is not limited to the forms described above, and other shapes may also be used. Moreover, the materials mentioned above are merely examples and are not limited to these. Furthermore, any additions, deletions, design changes, or appropriate combinations of structural examples of features from the embodiments obtained by those skilled in the art, as long as they remain within the scope of the spirit of this invention, are included within the scope of this invention.

[0093] The reference numerals in the attached figures are explained as follows: 1…Magnetic components 1A, 1B, 2A, 2B… Verification components 10… magnetic core 11… magnetic core 12…Midfoot 13… Side foot 14…Connecting part 20…winding 21… Primary winding 22… Secondary winding 25…signal detection line 30…winding skeleton Ds…interval distance L, Ls… length L1…First Gap L2…Second Gap T…thickness W, Wc, Wi… width

Claims

1. A magnetic component, characterized in that, have: A magnetic core having at least one set of opposing legs, with the first gap L1 formed by the set of aforementioned legs; and The winding is wound around the aforementioned set of feet along the extension direction of the aforementioned set of feet, and is wound in multiple layers in a manner that overlaps in a direction substantially perpendicular to the aforementioned extension direction; The feature is that, at least in the region surrounding the aforementioned first gap L1, the aforementioned winding is composed of multiple single-strand bundles of magnetically plated Litz wire, and The driving frequency is 200kHz or higher.

2. The magnetic component according to claim 1, comprising a coil including the aforementioned winding wound around the aforementioned set of feet. A second gap L2 is provided between the aforementioned coil and the aforementioned set of feet. The aforementioned second gap L2 and the aforementioned first gap L1 satisfy L2 2 / L1≤1.

6.

3. The magnetic component according to claim 2, wherein the aforementioned winding is composed of the aforementioned magnetically coated Litz wire and a single wire or Litz wire.

4. The magnetic component according to claim 1, when the interval distance between it and the aforementioned first gap L1 is set to Ds, The aforementioned winding located in Ds 2 The near-position winding within the range of / L1≤1.6 includes a portion composed of the aforementioned magnetically coated Litz wire.

5. The magnetic component according to claim 3, wherein the outer diameter of the aforementioned magnetic coating Litz wire or the outer diameter of the aforementioned Litz wire is different from the outer diameter of the aforementioned single wire.

6. An electrical / electronic machine, characterized in that, The device is equipped with the magnetic component as described in any one of claims 1 to 5.

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