Integrated magnetic component

Abstract

An integrated magnetic component 300 comprises: a magnetic core 310 having first and second magnetic circuits sharing a common core section 31, and arranged at different sides of the common core secti

Description

Technical Field The present disclosure relates to an integrated magnetic component and a method of assembling the same. More particularly, but not exclusively, the present disclosure relates to an integrated multi-phase inductor module for use with power conversion circuits. Background The rapid growth of wide bandgap (WBG) semiconductor devices, particularly Silicon Carbide (SiC) MOSFETs, in applications like electric vehicle (EV) inverters, renewable energy, industrial drives, railway traction, and uninterruptible power supply (UPS) systems presents a critical technical challenge. SiC MOSFETs enable higher switching frequencies, which in turn require smaller and more affordable filter inductors. However, to fully harness the potential of SiC technology, the design of associated magnetic components must also be optimized. Magnetic components account for 20% to 40% of the total weight and losses in power electronic converters, and reducing their weight is crucial to enhancing system efficiency, power density, and achieving more compact designs. In photovoltaic (PV) inverters, the need for efficient output LC or LCL filters to interface with the grid and filter out harmonics poses another technical problem. Optimizing AC filter inductors is critical to reducing size, weight, losses, temperature rise, and improving electromagnetic interference (EMI) and noise performance. Three-phase AC filter inductors can be designed as either discrete or integrated types. Discrete inductors offer magnetic decoupling, but they also increase the weight, volume, and cost of the system. The challenge lies in reducing these drawbacks while improving system performance and maintaining competitive market pricing. One of the known solutions to this problem is to integrate the magnetic cores of three-phase AC filter inductors. Known integrated inductors are disclosed in the following documents: • Research article titled “Research on the Comparison Analyses of Three-Phase Discrete and Integrated LC Filters in Three-Phase PV Inverter”, International Journal of Photoenergy, Volume 2013, Article ID 217023, available at http: / / dx.doi.org / 10.1155 / 2013 / 217023 • United States Patent Application US 2022 / 0208425 A1 • United States Patent Application US 2023 / 0085737 A1 • United States Patent Application US 2021 / 0366650 A1 The research article has compared three-phase discrete filter inductors with two types of integrated three-phase filter inductors in photovoltaic (PV) inverters. The findings indicate that integrated filter inductors have significantly smaller volumes. Specifically, the five-limb integrated inductors are one-third the size of their discrete counterparts, while the three-limb integrated inductors are two-thirds smaller. However, the coupling coefficient of the three-limb integrated inductor is 50%, meaning the current ripple in one phase is significantly influenced by the other two phases. The article does not clearly disclose the coupling coefficient for the five-limb integrated design, raising questions about whether the three inductors can be effectively decoupled. Furthermore, it remains unproven whether any of the three magnetic cores in the integrated filter inductor designs could saturate under worst-case operating conditions. US 2022 / 0208425A1, US 2023 / 0085737A1 and US 2021 / 0366650A1 disclose various forms of integrated inductor modules integrating two or more inductors. Generally speaking, the coupling coefficients between the integrated inductors remain relatively high. Due to the high coupling coefficients, and consequently higher mutual inductance, the current ripple in one inductor can be influenced by the other inductors. In US 2021 / 0366650A1, the coupling coefficient or mutual inductance between the integrated inductors is not specified, raising questions about whether the integrated inductors can be effectively decoupled. Further, it remains unclear how self-inductances of the inductors under DC bias can be increased, especially at higher current ratings such as 400A or 500A. It is an object of the present disclosure, among others, to provide an improved integrated magnetic component which solves one or more problems associated with known integrated inductors, whether identified herein or otherwise. Summary According to a first aspect of the present disclosure, there is provided an integrated magnetic component comprising: a magnetic core comprising: a first magnetic circuit and a second magnetic circuit which share a common core section, wherein the first and second magnetic circuits are arranged at different sides of the common core section, and the second magnetic circuit comprises a magnetic pillar attached to a surface of the common core section; at least one first winding operatively associated with the first magnetic circuit to form a first inductor; and at least one second winding operatively associated with the second magnetic circuit to form a second inductor, wherein the at least one second winding comprises a winding wound around the magnetic pillar. The expression “integrated” means that the magnetic component is of a unitary structure and can be handled as a single-piece item. The integrated magnetic component is therefore in contrast to multiple, separable, magnetic components. In particular, the magnetic core of the integrated magnetic component is an integrated core and also has a unitary structure. The integration is achieved by joining the first and second magnetic circuits with a common core section, which also directly supports a magnetic pillar (around which a winding is wound) of the second magnetic circuit. The integrated design consolidates first and second inductors into a single compact component, reducing both the component count and overall footprint. Such a configuration makes the component ideal for high-density applications. Furthermore, by arranging the first and second magnetic circuits at different sides of the common core section, the first and second magnetic circuits can be readily decoupled from one another, thereby improving the efficiency of systems using the integrated magnetic component and reducing noise and electromagnetic interference (EMI). The expression “the first and second magnetic circuits are arranged at different sides of the common core section” means that, apart from the shared common core section, the remaining portions of the first and second magnetic circuits are located at different sides of the common core section and do not share any additional common core section(s). The expression “operatively associated with” means that the winding is wound around at least one magnetic core section of the respective magnetic circuit. The integrated magnetic component may be for use in power applications. The first and second magnetic circuits may be stacked along a direction which is substantially perpendicular to the surface of the common core section. In other words, the first and second magnetic circuits may be arranged at opposite sides of the common core section. The expression “substantially perpendicular” or “generally perpendicular” allows for a deviation of up to 10% from the ideal orthogonal angle of 90°. When viewed along a direction perpendicular to the surface of the common core section, the first and / or second magnetic circuit may remain completely within a boundary of the common core section. The common core section may comprise a magnetic material which has a higher magnetic permeability than a magnetic material of the magnetic pillar. The mutual coupling coefficient between the first and second inductors may be less than around 2%. The mutual coupling coefficient between the first and second inductors may be less than around 0.75%. The magnetic permeability of the magnetic material of the common core section may be more than five times higher than the magnetic permeability of the magnetic material of the magnetic pillar. The magnetic permeability of the magnetic material of the common core section may be more than ten times higher than the magnetic permeability of the magnetic material of the magnetic pillar. The common core section may comprise a magnetic material with a relative magnetic permeability of at least 500. Preferably, the magnetic material of the common core section may have a relative magnetic permeability of at least 800. More preferably, the magnetic material of the common core section may have a relative magnetic permeability of at least 1000. The common core section may be free from any air gap. In other words, the common core section is made solely of magnetic material(s). The magnetic pillar may comprise one or more air gaps. The integrated magnetic component may further comprise one or more layers of nonmagnetic material(s) arranged within the one or more air gaps. The magnetic pillar may be of an elongated shape. The magnetic pillar may extend along a direction generally perpendicular to the surface of the common core section. In other words, a central axis of the magnetic pillar may be generally perpendicular to the surface of the common core section. The one or more air gaps may divide the magnetic pillar into a plurality of split pillars arranged along the direction generally perpendicular to the surface of the common core section. Each air gap may have a length of no greater than 2 mm along the direction generally perpendicular to the surface of the common core section. Preferably, each air gap may have a length of no greater than 1 mm along the direction generally perpendicular to the surface of the common core section. The magnetic pillar may comprise a magnetic material with a relative magnetic permeability of no greater than 250. Preferably, the magnetic material of the magnetic pillar may have a relative magnetic permeability of no greater than about 150. The magnetic material of the magnetic pillar may have a relative magnetic permeability of no greater than about 90. More preferably, the magnetic material of the magnetic pillar may have a relative magnetic permeability of no greater than about 60. The term “about” or “around” used in the present disclosure indicates a degree of variability (e.g., ±20%) in the stated numerical values. Each of the first and second magnetic circuits may be a closed-loop magnetic circuit. It would be understood that a closed-loop magnetic circuit refers to a type of magnetic circuit where the magnetic flux is confined to a continuous, closed path with minimal leakage. A closed-loop magnetic circuit may comprise small air gap(s) (e.g., the one or more air gaps as described above), provided that the air gap(s) are not long enough to cause significant leakage of magnetic flux into the surroundings. The surface of the common core section may be a second surface and faces the at least one second winding, and the common core section may further comprise a first surface that faces the at least one first winding. The first magnetic circuit may comprise a further magnetic pillar attached to the first surface of the common core section. The at least one first winding may comprise a further winding wound around the further magnetic pillar. The second surface may be opposite to the first surface. The common core section may have a plate-like shape. Each of the first and second surfaces may be generally flat. The second surface may be generally parallel (e.g., with a small angle of no greater than about 5°) to the first surface. The first magnetic circuit may comprise a first magnetic pillar and a second magnetic pillar, both attached to the first surface of the common core section. The first magnetic circuit and the at least one first winding may be configured such that a current flowing through the first inductor generates magnetic flux along a first direction within the first magnetic pillar and generates magnetic flux along a second direction within the second magnetic pillar, and the first and second directions may be opposite to one another. The first and second magnetic pillars may be spaced apart from one another along a direction parallel to the first surface of the common core section. The first and second directions may be generally perpendicular to the first surface of the common core section. Each of the first and second magnetic pillars may extend along a direction generally perpendicular to the first surface of the common core section. In other words, a central axis of each of the first and second magnetic pillars may be generally perpendicular to the first surface of the common core section. The at least one first winding may comprise a first winding wound around the first magnetic pillar and a second winding wound around the second magnetic pillar. The first and second windings may be interconnected, so as to collectively form a part or the whole of the first inductor. It would be understood that the current flowing through the first inductor flows through the first and second windings in opposite directions (e.g., clockwise and anticlockwise), thereby inducing magnetic fluxes of opposite directions within the first and second magnetic pillars. The magnetic pillar of the second magnetic circuit may be a third magnetic pillar, and the second magnetic circuit may further comprise a fourth magnetic pillar attached to the second surface of the common core section. The second magnetic circuit and the at least one second winding may be configured such that a current flowing through the second inductor generates magnetic flux along a third direction within the third magnetic pillar and generates magnetic flux along a fourth direction within the fourth magnetic pillar; and the third and fourth directions may be opposite to one another. Each of the third and fourth magnetic pillars may extend along a direction generally perpendicular to the second surface of the common core section. In other words, a central axis of each of the third and fourth magnetic pillars may be generally perpendicular to the second surface of the common core section. The third and fourth directions may be generally perpendicular to the second surface of the common core section. The third and fourth magnetic pillars may be spaced apart from one another along a direction parallel to the second surface of the common core section. The winding of the at least one second winding may be a third winding wound around the third magnetic pillar, and the at least one second winding may further comprise a fourth winding wound around the fourth magnetic pillar. The third and fourth windings may be interconnected, so as to collectively form a part or the whole of the second inductor. It would be understood that the current flowing through the second inductor flows through the third and fourth windings in opposite directions, thereby inducing magnetic fluxes of opposite directions within the third and fourth magnetic pillars. When viewed along a direction perpendicular to the surface of the common core section, the first magnetic pillar may be generally aligned with one of the third and fourth magnetic pillars, and the second magnetic pillar may be generally aligned with the other of the third and fourth magnetic pillars. The expression “generally aligned with” means that the relevant magnetic pillars substantially overlap with one another, e.g., the centres of the relevant pillars being no more than 30% of a diameter of either pillar apart. The first magnetic circuit may further comprise a first core section connecting the first magnetic pillar and the second magnetic pillar. The first core section may be located at an end of the magnetic core along a direction perpendicular to the surface of the common core section. Each of the first and second magnetic pillars may be arranged between the common core section and the first core section. The at least one first winding may encircle or be wound around one or more of the first and second magnetic pillars and the first core section. The first core section may comprise a magnetic material with a relative magnetic permeability of no greater than 150. The second magnetic circuit may comprise a second core section connecting the third and fourth magnetic pillars. The second core section may be located at an opposite end of the magnetic core along the direction perpendicular to the surface of the common core section, or may be a common core section shared by the second magnetic circuit and a third magnetic circuit. When viewed along a direction perpendicular to the surface of the common core section, the first and / or second magnetic circuit may remain completely within a boundary of the first or the second core section. The common core section may be a first common core section, and the magnetic core may further comprise a third magnetic circuit which shares a second common core section with the second magnetic circuit. The second and third magnetic circuits may be arranged at different sides of the second common core section. The integrated magnetic component may further comprise at least one third winding operatively associated with the third magnetic circuit to form a third inductor. The second common core section may connect the third magnetic pillar and the fourth magnetic pillar. Each of the third and fourth magnetic pillars may be arranged between the first common core section and the second common core section. The at least one second winding may be wound around one or both of the third and fourth magnetic pillars. One or more of the first core section and the common core section(s) may have a platelike shape (i.e., with opposing, substantially flat, surfaces). Each of the first, second and third inductors may be a standalone inductor. In other words, the first, second, and third inductors are separate from one another (unless externally connected) and can be individually energised. Consequently, they can operate independently of one another. According to a second aspect of the present disclosure, there is provided a system comprising: a power conversion circuit comprising a plurality of AC phases, wherein the plurality of AC phases comprise a first AC phase and a second AC phase; and an integrated magnetic component according to any preceding claim, wherein the first inductor of the integrated magnetic component is electrically coupled to the first AC phase, and the second inductor of the integrated magnetic component is electrically coupled to the second AC phase. It would be understood that the AC phases may be either inputs or outputs of the power conversion circuit. The term “electrically coupled” includes the possibility that one or more intervening elements may be present between the coupled elements. The system may be configured such that, during an operation of the system: a first electrical current flows between the first AC phase and the first inductor and a second electrical current flows between the second AC phase and the second inductor; the first electrical current generates first magnetic flux within the first magnetic circuit, and the first magnetic flux flows through the common core section along a fifth direction; the second electrical current generates second magnetic flux within the second magnetic circuit, and the second magnetic flux flows through the common core section along a sixth direction; when the first and second electrical currents are of the same polarity, the fifth direction is the same as the sixth direction. The first and second electrical currents are typically AC currents that periodically reverse direction and change magnitude continuously with time. By using the expression “of the same polarity”, it is intended to mean that the first and second electrical currents flow in the same direction, i.e., either both flowing into the respective first and second inductors, or both flowing out of the respective first and second inductors. In other words, during part of a cycle, when the waveforms of the first and second electrical currents remain on the same side of the zero Ampere line, the first and second electrical currents are considered to be of the same polarity. Each of the first and second electrical currents may comprise a power-frequency current component and a high-frequency current component, with the high-frequency current component having a higher frequency than the power-frequency current component. The fifth and sixth directions may be parallel to the surface of the common core section. A phase difference between the first electrical current and the second electrical current may be 360 / N, with N being a total number of the AC phases of the power conversion circuit. According to a third aspect of the present disclosure, there is provided a method of assembling an integrated magnetic component, comprising: forming a first magnetic circuit and a second magnetic circuit within a magnetic core of the integrated magnetic component, wherein the first and second magnetic circuits share a common core section and are arranged at different sides of the common core section, and wherein the second magnetic circuit comprises a magnetic pillar attached to a surface of the common core section; operatively associating at least one first winding with the first magnetic circuit to form a first inductor; and operatively associating at least one second winding with the second magnetic circuit to form a second inductor, wherein the at least one second winding comprises a winding wound around the magnetic pillar. Where appropriate any of the features described above in relation to any aspect of the present disclosure may be applied to any other aspect of the disclosure. It would also be understood that the terms “first” to “sixth” are simply used in the present disclosure to label the relevant elements for the ease of description, and do not imply any limitations to the sequence, location or the total number of the relevant elements. Brief Description of the Drawings In order that the disclosure may be more fully understood, a number of embodiments of the disclosure will now be described, by way of example, with reference to the accompanying drawings, in which: Figure 1 illustrates: (a) a schematic diagram of a three-phase inverter circuit; and (b) a schematic diagram of a three-phase power factor correction (PFC) circuit; Figure 2 schematically illustrates a perspective view of an integrated magnetic component according to an embodiment of the present disclosure; Figure 3 schematically illustrates a front view of the integrated magnetic component of Figure 2; Figure 4 schematically illustrates a side view of the integrated magnetic component of Figure 2; Figure 5 schematically illustrates a bottom view of the integrated magnetic component of Figure 2; Figure 6 schematically illustrates a perspective view of a magnetic core used in the integrated magnetic component of Figure 2; Figure 7 schematically illustrates a front view of the magnetic core of Figure 6; Figure 8 illustrates an exemplary set of windings for use within one phase of the inductor; Figure 9 schematically illustrates a front view of a first embodiment of the integrated magnetic component when three sets of windings are wound around the magnetic core; Figure 10 schematically illustrates the electrical connections between the three-phase inverter circuit of Figure 1(a) and the integrated magnetic component of Figure 9; Figure 11 schematically illustrates the distribution of magnetic flux in the magnetic core according to the first embodiment of Figure 9; Figure 12 schematically illustrates a front view of a second embodiment of the integrated magnetic component when three sets of windings are wound around the magnetic core; Figure 13 schematically illustrates the distribution of magnetic flux in the magnetic core according to the second embodiment of Figure 12; Figure 14 shows time-domain waveforms of the three-phase winding currents of the integrated magnetic component when used in the circuits of Figure 1 and 10; Figure 15 shows processing steps of a method for assembling an integrated magnetic component according to an aspect of the present disclosure. In the figures, like parts are denoted by like reference numerals. It will be appreciated that the drawings are for illustration purposes only and are not drawn to scale. Detailed Description of the Preferred Embodiments Figures 1(a) and 1(b) illustrate schematic diagrams of a three-phase inverter circuit (with a DC-to-AC converter) and a three-phase power factor correction (PFC) circuit (with an AC-to-DC converter), respectively, each containing three inductors La, Lb, and Lc. The three-phase inverter circuit of Figure 1(a) may be a grid-connected solar inverter circuit. The three inductors La, Lb, and Lc are connected to the three AC phases of the power converter. Generally speaking, the current passing through each individual inductor is composed of two distinct components: a power-frequency current component, which corresponds to the fundamental operating frequency of the system, and a high-frequency current component, which exists at frequencies above the primary power frequency. These two components together define the overall current flowing through each inductor within the three-phase configuration. By way of an example, the power-frequency current component typically operates at frequencies up to 60 Hz, such as 50 Hz or 60 Hz sinusoidal currents. In contrast, the high-frequency current component corresponds to the switching frequency of the switching device within the power converter, which is generally above 16 kHz. The present disclosure provides an integrated magnetic component 300 which integrates the three inductors La, Lb, and Lc into a single module. A magnetic component is an electronic component that uses magnetism as a functional principle to manipulate electrical energy. These components are fundamental in power electronics, signal processing, and other applications where energy transformation, transfer, or filtering is needed. The “integrated magnetic component” used in the present disclosure may be used interchangeably with “integrated magnetic module” or “integrated multi-phase inductor”. The exemplary structures of the integrated magnetic component 300 are schematically shown in Figures 2 to 11. With reference to Figures 6 to 7, the integrated magnetic component 300 includes a magnetic core 310, which is integrally formed and / or has a unitary structure. This means that different parts of the magnetic core 310 are connected together so as to make up a single complete piece, and so as to be incapable of being easily dismantled without destroying the integrity of the piece. A magnetic core is a material used to concentrate and guide magnetic flux in devices such as inductors, transformers, electromagnets, and magnetic sensors. By providing a low-reluctance path for magnetic flux, it improves the efficiency of these components, reduces energy losses, and enhances magnetic coupling. Different parts of the magnetic core 310 may be made of different materials as described below in more detail. In this example, the magntic core 310 forms three magnetic circuits correpsonding to the three-phase inductors La, Lb, and Lc, respectively. The first magnetic circuit is formed by a core section 30, two magnetic pillars 34A, 35A and a core section 31. The magnetic pillars 34A, 35A are spaced apart from one another along the X direction. The second magnetic circuit is formed by the core section 31, two magnetic pillars 34B, 35B and a core section 32. The magnetic pillars 34B, 35B are spaced apart from one another along the X direction. The third magnetic circuit is formed by the core section 32, two magnetic pillars 34C, 35C and a core section 33. The magnetic pillars 34C, 35C are spaced apart from one another along the X direction. The first and second magnetic circuits share the common core section 31, and the second and third magnetic circuits share the common core section 32. The first to third magnetic circuits are stacked along a stacking direction (i.e., Z direction), thereby forming an array along the Z direction. The core sections 30, 33 are located at opposite ends of the magnetic core 310 along the Z direction, while the common core sections 31, 32 are internal to the magnetic core 310. The core sections 31, 32 may be refered to as “first common core section” and “second common core section”, respectively. With reference to Figure 7, each of the first, second, and third magnetic circuits forms a closed-loop and has a substantially rectangular shape in the XZ plane. In this example, each of the core sections 30 to 33 is of a plate shape with a pair of flat surfaces (along the XY plane) formed at opposite sides of the respective core section. The flat surfaces are parallel to the XY plane and are perpendicular to the stacking direction Z. Therefore, the core sections 30 to 33 may also be referred to as magnetic plates, and the core sections 30, 33 may be referred to as end plates. However, it would be understood that other shapes of the core sections 30 to 33 are possible. The magnetic pillars 34A to 34C and 35A to 35C are used as winding columns for supporting respective windings of the integrated inductors. Each of the magnetic pillars 34A to 34C and 35A to 35C is of an elongated shape and extends generally along the stacking direction Z (i.e., with the central axis being substantially parallel to the Z direction). In particular, the magnetic pilllars 34A and 35A extend between a lower surface of the common core section 31 and an upper surface of the end core section 30; the magnetic pilllars 34B and 35B extend between a lower surface of the common core section 32 and an upper surface of the common core section 31; and the magnetic pilllars 34C and 35C extend between a lower surface of the end core section 33 and an upper surface of the common core section 32. The term “magnetic pillar” may be used interchangeably with “winding column”. In this example, the core sections 30 to 33 have the same size along the XY plane and are aligned with one another when viewed along the Z direction. Further, the magnetic pillars 34A to 34C and 35A to 35C are attached to the surfaces of the core sections 30 to 33 and do not protrude over the boundaries of the core sections 30 to 33 as defined in the XY plane (as shown in Figure 5). Therefore, when viewed along the Z direction, each of the first to third magnetic circuit remains completely within the boundary of the common core section 31 or 32 or within the boundary of the end core section 30 or 33. As shown in Figures 6 and 7, the winding column 34A includes four split cores 341A, 342A, 343A, and 344A and three air gaps 3411 A, 3421 A, and 3431A between the adjacent split cores. In other words, the presence of the air gaps 3411A, 3421 A, and 3431A divide the winding column 34A into four split cores 341A, 342A, 343A and 344A. Each of the air gaps generally extends along the XY plane. The split cores 341A, 342A, 343A and 344A are arranged along the Z direction. Similarly, the winding column 35A consists of four split cores 351A, 352A, 353A, and 354A and three air gaps 3511 A, 3521 A, and 3531A between the adjacent split cores. Likewise, the winding column 34B consists of four split cores 341B, 342B, 343B, and 344B and three air gaps 3411B, 3421B, and 3431B. The winding column 35B has four split cores 351B, 352B, 353B, and 354B and three airgaps 3511B, 3521B, and 3531B. Similarly, the winding column 34C consists of four split cores 341C, 342C, 343C, and 344C and airgaps 3411C, 3421C, and 3431C, and the winding column 35C consists of four split cores 351C, 352C, 353C, and 354C and air gaps 3511C, 3521C, and 3531C. To improve the structural integrity of the winding columns, non-magnetic material(s) are placed within the air gaps described above. For example, one or more layers of paper or Kapton tape may be arranged between any pair of the adjacent split cores to create an air gap. Adhesives may be used to securely attach the paper and / or kapton tape to the split cores, thereby maintaining the shape of each winding column. The length of each air gap along the Z direction is equal to the total thickness of the non-magnetic material(s) between the adjacent split cores. Preferably, the length of each air gap is not long enough to cause noticeable leakage of magnetic flux into surroundings. Each air gap may have a length of no greater than 2 mm along the Z direction. More preferably, each air gap may have a length of no greater than 1 mm along the Z direction. With further reference to Figures 6 and 7, when viewed along the Z direction, the rightside magnetic pillars 34A to 34C are generally aligned with one another, and similarly the left-side magnetic pillars 35A to 35C are generally aligned with one another. In this example, the centres of the relevant pillars are coincident with (i.e., aligned with) each other when viewed along the Z direction. It would however be appreciated that a slight offset between the centres of the relevant pillars (e.g., no greater than 30%, preferably no greater than 10%, of a diameter of each pillar) may be introduced without substantially affecting the performance of the component 300. Figures 2 to 5 show different views of the integrated magnetic component 300 when windings are wound around the magnetic pillars 34A to 34C and 35A to 35C. In particular, windings 36A and 37A are wound around the respective magnetic pillars 34A and 35A, and are interconnected to form the phase A inductor La. The interconnection between the windings 36A and 37A is however not shown in Figures 2 to 5. Similarly, windings 36B and 37B are wound around the respective magnetic pillars 34B and 35B, and are interconnected to form the phase B inductor Lb. Windings 36C and 37C are wound around the respective magnetic pillars 34C and 35C, and are interconnected to form the phase C inductor Lc. The windings 36A and 37A may be collectively referred to as “at least one first winding”, and the windings 36B and 37B may be collectively referred to as “at least one second winding”. The windings between different phases are not connected within the component 300 itself. Therefore, the integrated magnetic component 300 provides three standalone inductors which can be individually energised and can operate independently of each other. In the example of the integrated magnetic component 300 as shown by Figures 2 to 7, the integration of three-phase inductors is achieved by joining two sets of magnetic pillars (i.e., 34A&35A and 34B&35B) for phases A and B with a common core section 31 in between, and by joining two sets of magnetic pillars (i.e., 34B&35B and 34C&35C) for phases B and C with a common core section 32 in between. The integrated design consolidates all three phases into a single compact component, reducing both the component count and overall footprint. By optimizing material use and reducing redundant winding sections (which were otherwise used in some of the known integrated inductors), the integrated design of the present disclosure operates with higher efficiency, lower power dissipation, and reduced manufacturing and assembly costs. This makes the component ideal for high-density applications, such as electric vehicles, photovoltaic (PV) systems, railway traction, industrial drives, and energy storage solutions. The reduced size not only saves valuable space on circuit boards but also simplifies manufacturing, resulting in lower production costs-crucial for scalable deployment in modern power electronic systems. By forming air gaps within the magnetic pillars 34A to 34C and 35A to 35C, the magnetic flux induced within the core 310 can be fine-tuned, and risks of core saturation at high currents are reduced, thereby effectively preventing excessive losses from occurring in the component 300. By lowering overall losses, the integrated magnetic component 300 has an improved efficiency and power density. Further, the inventor of the present dislcosure has found that the use of air gaps can effectively enhance self-inductance of the AC inductors at high current ratings, such as 400A or 500A. Therefore, the integrated magnetic component 300 provides enhanced inductance stability compared to conventional integrated inductors, especially under high DC bias conditions, where traditional inductors often suffer from performance degradation. In addition, the air gaps may facilitate efficient heat dissipation from the magnetic core 310 to ambient environment. Figure 8 shows an example of the windings 36A and 37A for phase A inductor La. It can be seen that the windings 36A and 37A are connected at the bottom. The windings 36A and 37A are designed such that a current flowing through the phase A inductor La flows in opposite directions through the windings 36A and 37A. As shown in Figure 8, the current flows in the anticlockwise direction within the winding 36A, creating a magnetic field along the Z direction. In contrast, the current flows in the clockwise direction within the winding 37A, generating a magnetic field along the -Z direction. Therefore, when the windings 36A and 37A are placed around the respective winding columns 34A and 35A, opposing magnetic fields are induced within these winding columns. The windings 36B and 37B for phase B inductor Lb, and the windings 36C and 37C for phase C inductor Lb, may be constructed in a similar manner to those showin in Figure 8. Figure 9 shows a first embodiment of the integrated magnetic component 300 where the windings for all three phases are schematically illustrated. Figure 10 shows the electrical connections between the integrated magnetic component 300 and a three-phase DC-to-AC power inverter 400. The power inverter 400 outputs three AC phases. The three inductors La, Lb, Lb formed by the integrated magnetic component 300 are electrially connected to the respective three AC phases. In this way, the three AC currents Ia, Ib, output by the AC phases flow into the input nodes 40A to 40C (shown in Figures 9 and 10) of the respective inductors before flowing out of the respective output nodes 42A to 42C of the inductors. With reference to Figure 9, the windings 36B and 37B for phase B inductor Lb, and the windings 36C and 37C for phase C inductor Lc are constructed in the same way as the windings 36A and 37A for phase A inductor La. For ease of understanding, it is assumed that the three AC currents Ia, Ib, k share the same direction (or polarity), e.g., all the three AC currents are positive and flow into the input nodes 40A to 40C of the inductors. In this case, the directions of the magnetic fluxes generated by the currents are shown in Figure 11. Following the direction of each current 1^, Ib, k. the current flows in a clockwise direction through the windings 37C, 37B and 37A, and flows in an anticlockwise direction through the windings 36C, 36B and 36A. With reference to Figures 9 and 11, the current flowing through winding 36A is opposite in direction to the current flowing through winding 37A, resulting in opposing magnetic fields being induced within the winding columns 34A and 35A. Similarly, the current flowing through winding 36B is opposite in direction to the current flowing through winding 37B, inducing opposing magnetic fields within the winding columns 34B and 35B. Likewise, the direction of the current flowing through winding 36C is opposite in direction to the current flowing through winding 37C, resulting in opposing magnetic fields being induced within the winding columns 34C and 35C. In the embodiment of Figure 9, the common core sections 31, 32 are made of a magnetic material with a higher magnetic permeability than the magnetic material used for the winding columns 34A to 34C and 35A to 35C. For example, the permeability of the magnetic material in the common core sections 31 and 32 may be more than five times (preferably, more than ten times) higher than that of the magnetic material in the winding columns 34A to 34C and 35A to 35C. In another example, the relative permeability of the magnetic material in the common core sections 31 and 32 may be at least 500 (preferably at least 800, or more preferably at least 1000), while the relative permeability of the magnetic material in the winding columns 34A to 34C, 35A to 35C is no greater than 250 (preferably no greater than 150; more preferably no greater than 90 or 60). For instance, the common core sections 31 and 32 may be made from high-permeability materials, such as amorphous or nanocrystalline materials, with a relative permeability pr 3s 1000. Furthermore, the common core sections 31 and 32 are free from any air gaps therein. These factors enable each of the common core sections 31 and 32 to have low magnetic reluctance. On the other hand, the winding columns 34A to 34C, 35A to 35C may be constructed from alloy powder cores with low magnetic permeability (such as Ni-Fe, Fe-Si, Fe-Si-AI, etc.) with a relative permeability pr <90. As described above, each of the winding columns include three air gaps. Due to the low-permeability material and air gaps, the magnetic reluctance of each winding column is significantly higher than that of each common core section 31 and 32. These designs of the common core sections 31 and 32 effectively decouple the magnetic circuits for phases A and B, as well as for phases B and C. In the embodiment shown in Figure 9, the maximum coupling coefficient between any two phases can be lower than 2%. As a result, as shown in Figure 11, the first magnetic flux, 0a, generated by the current in phase A, flows within a closed-loop magnetic circuit composed of the winding column 35A, the bottom core section 30, the winding column 34A, and the common core section 31. This configuration effectively minimizes flux leakage to phase B, owing to the low reluctance of the common core section 31. Similarly, the second magnetic flux, 0b, produced by the current Ib in phase B, flows within a closed-loop magnetic path formed by winding column 35B, common core section 31, winding column 34B, and common core section 32. This setup significantly reduces flux leakage to phases A and C due to the low reluctances of common core sections 31 and 32. Likewise, the third magnetic flux, 0c, generated by the current in phase C, follows a closed-loop magnetic circuit formed by winding column 35C, common core section 32, winding column 34C, and top core section 33, further reducing flux leakage to phase B due to the low reluctance of the common core section 32. The low coupling coefficient between adjacent phases also ensures superior phase isolation, reduces noise and electromagnetic interference (EMI), and provides cleaner, more stable power delivery. This feature represents a significant improvement over conventional integrated inductors, which typically suffer from higher inter-phase coupling and greater noise generation, thereby ensuring higher-quality power conversion. More specifically, as each of the magnetic fluxes 0a, 0b, and 0c circulates within its own closed-loop magnetic circuit, the likelihood of magnetic flux leakage into the air is significantly reduced. As a result, the integrated magnetic component 300 excels in EMI suppression and eliminates the need for additional shielding. This simplifies the system design, reduces overall complexity, and ensures compliance with stringent EMI standards, which is an essential factor for applications in automotive, aerospace, and consumer electronics. Using high-permeability material(s) for the common core sections is also beneficial in reducing the overall volume of the integrated magnetic component 300, as the thickness of the common core sections 31 and 32 may be reduced while still achieving relatively low magnetic reluctance and, consequently, low coupling coefficients between adjacent phases. Alternatively, the common core sections 31 and 32 may be made from alloy powder cores with low magnetic permeability (such as Ni-Fe, Fe-Si, Fe-Si-AI, etc., with permeability pr 150), but without air gaps. However, using low-permeability material for the common core sections 31 and 32 may increase the coupling coefficient between different phases. To mitigate this, the thickness or cross-sectional area of the common core sections 31 and 32 may be increased to reduce the coupling coefficient and improve phase isolation. This approach, however, also increases volume, cost, and power loss. The lower core section 30 and the upper core section 33 may be constructed from alloy powder cores with low magnetic permeability (such as Ni-Fe, Fe-Si, Fe-Si-AI, etc., with permeability pr 150) but without air gaps, to optimize inductance under no-load conditions or at low currents. Preferably, the relative permeability of the core sections 30 and 33 is within the range of 75 <pr 150. However, this can be adjusted to lower permeability values (pr 75) to optimize performance under varying operational conditions. Lowering the permeability may reduce inductance at lower currents but can improve inductance stability at higher currents. This adjustment helps maintain a more consistent inductance profile, particularly under high DC bias conditions, thereby enhancing stability and efficiency across a range of load conditions. Figures 12 and 13 show a second embodiment of the integrated magnetic component 300’. Elements of the component 300’ that are identical to those of the component 300 are identified using the same labels. Elements of component 300’ that correspond to, but differ from those of component 300, are labelled using the same numerals but with a prime symbol (’) for differentiation. The features and advantages described above with reference to the first embodiment are generally applicable to the second embodiment. The component 300’ is connected to the three-phase DC-to-AC power inverter 400 in the same way as shown in Figure 10. The component 300’ differs from the component 300 in that the windings 37C and 36C of the inductor Lc are constructed in the same way as the windings 37A and 36A of the inductor La, but the windings 37B’ and 36B’ of the inductor Lb are constructed differently. Again, assuming that the three AC currents 1^, Ib, and share the same direction (or polarity), e.g., the three AC currents all being positive currents flowing into the input nodes 40A to 40C of the inductors, the directions of the magnetic fluxes generated by the currents are shown in Figure 13. Following the direction of each current Ib, and the current flows in a clockwise direction through the windings 37C, 36B’ and 37A, and flows in an anticlockwise direction through the windings 36C, 37B’ and 36A. With reference to Figures 12 and 13, the current flowing through the windings 36A and 37A, wound around the winding columns 34A and 35A, generates a first magnetic flux 0a which is anticlockwise in the XZ plane. It is understood that the magnetic flux follows the same direction as the induced magnetic field. Similarly, the current flowing through the windings 36B’ and 37B’, wound around the winding columns 34B and 35B, generates a second magnetic flux 0b which is clockwise in the XZ plane. The current flowing through the windings 36C and 37C, wound around the winding columns 34C and 35C, generates a third magnetic flux 0c which is anticlockwise in the XZ plane. Therefore, the first magnetic flux 0a and the second magnetic flux 0b are in the same direction on the common core section 31, and the superimposed magnetic flux in the common core section 31 is the sum of 0a and 0b. Similarly, the second magnetic flux 0B,and the third magnetic flux 0c are in the same direction on the common core section 32, and the superimposed magnetic flux in the common core section 32 is the sum of 0b and 0c. This is in contrast to Figure 11, which shows the magnetic fluxes generated by the currents in the magnetic core 310 of the component 300 illustrated by Figure 9. With reference to Figure 11, the magnetic fluxes 0a, 0b, and 0c induced by the currents Ia, Ib, ic , are all along an anticlockwise direction within their respective magnetic circuits in the XZ plane. It can be seen that the first magnetic flux 0a and the second magnetic flux 0b are in opposite directions on the common core section 31. Hence, the superimposed magnetic flux in the common core section 31 is the difference between 0a and 0b. Similarly, the second magnetic flux 0b and the third magnetic flux 0c are in opposite directions on the common core section 32. Hence, the superimposed magnetic flux in the common core section 32 is the difference between 0b and 0c. As compared to the first embodiment in Figures 9 and 11, the second embodiment as illustrated by Figures 12 and 13, achieves even lower coupling coefficients between different phases, along with reduced core losses and improved thermal peformance. This is explained below. When the integrated magnetic component 300 (or 300’) is used in the application as shown in Figure 10 (or Figure 1(b)), the current passing through each individual inductor is composed of two distinct components: a power-frequency current component and a high-frequency current component. Therefore, the three-phase AC currents 1^, Ib, and may be represented as follows: IA (') = K: Sin (2^ / ) + IAC • Triangular I., (r) = I,,.. Sin [inTt + 120° Xi + I... • Triangular fu,t + — D \ J I'C y Lr y AC I nr ( a Ir = I nr Sin {inf, rt + 240°^ + I ,r • Triangular] f„rt + ---- C \ J DC y / . / ' / AC / / / ' Q / ? wherein, Triangular represents a triangular waveform function, fLp is the frequency of the power-frequency current component, fap is the frequency of the high-frequency current component (e.g., the switching frequency of a PFC or inverter circuit), Idc is the amplitude of the power-frequency current component, and Iac is the amplitude of the high-frequency current component. Generally, the phases of the power-frequency current components are offset by 120° relative to each other. Consequently, the phases of the magnetic fluxes induced by the power-frequency current components are similarly offset by 120°. Typically, the vector sum of the three-phase power-frequency current components equals zero. Thus, the vector sum of the three-phase magnetic fluxes induced by the power-frequency current components also equals zero. Figure 14 shows the waveforms of the three-phase AC currents Ib, and i^. In this example, Iac'is much smaller than Idc- The three-phase AC currents periodically reverse direction and change magnitude continuously with time. According to Hopkinson's law, the magnetic flux (either magnitude or phase) induced by a coil is closely associated with the magnitude and phase of the current flowing in the coil. Therefore, superimposed currents between different phases may be treated as representations of superimposed magnetic fluxes in the common core sections 31 and 32. Figure 14 shows the waveforms of superimposed currents + Ib (which represent superimposed fluxes 0a + 0b in the common core section 31 of Figure 13), superimposed + ic (which represent superimposed fluxes 0b + 0c in the common core section 32 of Figure 13), superimposed currents - Ib (which represent superimposed fluxes 0a - 0b in the common core section 31 of Figure 11), superimposed Ib - ic (which represent superimposed fluxes 0b- 0c in the common core section 32 of Figure 11). It can be seen that the superimposed currents Ia + Ib , Ib + ic have lower amplitudes than the superimposed currents Ia - Ib, Ib - ic- Therefore, the integrated magnetic component 300’ of the second embodiment is expected to have reduced flux density in the common core sections 31 and 32, as compared to the integrated magnetic component 300 of the first embodiment. Lower flux density is generally beneficial for reducing core losses. Therefore, the integrated magnetic component 300’ is expected to have lower core losses than the integrated magnetic component 300. Furthermore, as compared to the integrated magnetic component 300, the integrated magnetic component 300’ further reduces the risks of core saturation in the common core sections 31 and 32 (because the flux densities in the common core sections 31 and 32 are further from their saturation flux densities), thereby effectively preventing excessive losses from occurring in component 300’. By lowering overall losses, the integrated magnetic component 300’ improves efficiency and power density, thereby enhancing the overall performance of the power electronic system. The integrated magnetic component 300’ also achieves improved thermal performance. By minimizing core losses and reducing thermal generation, the component operates at cooler temperatures, which is especially critical for high-power applications such as 350kW and 400kW systems in industrial drives and high-capacity inverters. This enhanced thermal efficiency contributes to long-term reliability and operational longevity, even in demanding environments. This improved thermal performance not only prevents heat-induced degradation of the component but also protects surrounding circuitry, enhancing the reliability and lifespan of the entire system. Further, the lower flux densities within the common core sections 31 and 32 of the integrated magnetic component 300’ are also beneficial for further reducing the maximum coupling coefficients between any two phases to a level of less than 0.75%. The inventor has investigated two integrated magnetic components that are otherwise identical to one another apart from the differences in the winding configuration of phase B as illustrated by Figures 9 and 12. In each of the integrated magnetic components, the core sections 30 and 33 are made of a magnetic material with a relative permeability of 75, without any air gap therein, and the winding columns are made of a magnetic material with a relative permeability of 26, each with three small air gaps as shown in Figures 6 and 7, and the common core sections 31 and 32 are made of a magnetic material with a relative permeability of 1000 without any air gap therein. Further, the thickness of each common core section 31 and 32 is around 28mm. The overall dimension of each integrated magnetic component is around 237.5mm (L) * 155mm (W) * 72 mm (H), and the total weight of each integrated magnetic component is around 12.97kg. The integrated magnetic component with the winding configuration of Figure 9 achieves a maximum coupling coefficient of 1.25% between phase A and phase B, and a maximum coupling coefficient of 1.24% between phase B and phase C. The integrated magnetic component with the winding configuration of Figure 12 achieves a maximum coupling coefficient of 0.74% between phase A and phase B, and a maximum coupling coefficient of 0.73% between phase B and phase C. Therefore, it is evident that by suitably designing the winding configurations of different phases such that magnetic fluxes generated by different phases superimpose on the common core section as a sum, the coupling coefficient between the different phases can be effectively reduced. It would be understood that the directions of the magnetic fluxes 0a and 0b as depicted in Figures 11 and 13 may occur during time window T1 (Figure 14) where the currents Ia and Ig both have positive polarity. Similarly, the directions of the magnetic fluxes 0b and 0c, as depicted in Figures 11 and 13 may occur during time window T2 (Figure 14) where the currents and both have positive polarity. It would also be understood that the flux distribution of Figure 13 can be achieved using the integrated magnetic component 300 of Figure 9, by swapping the input and output nodes 40B and 42B of phase B so as to modify the connections between the converter circuit 400 and the component 300. With such an arrangement, when both phase A and phase B currents are of the same polarity (e.g., both being positive current flowing into the inductors, or both being negative currents flowing out of the inductors), their induced magnetic fluxes are along the same direction on the common core section 31. Therefore, the magnetic fluxes generated by phases A and B superimpose on the common core section 31 as a sum. Similarly, the magnetic fluxes generated by phases B and C also superimpose on the common core section 32 as a sum. In summary, the integrated magnetic component 300 or 300’ addresses the limitations of traditional inductors by combining high efficiency, low coupling, compact size, thermal stability, and effective EMI suppression. Its ability to reduce core losses directly translates to improved overall system efficiency and performance, setting a new benchmark for modern power electronic systems. The present disclosure provides optimal solutions for both high-performance and high-reliability applications, offering substantial benefits in a variety of industries. The versatility of the integrated magnetic component 300 or 300’ further adds to its appeal. It can be used as an AC filter inductor in DC / AC string inverters or as a PFC inductor in AC / DC rectifiers, and can also be implemented in a wide range of power conversion systems. Specifically, it may be applied in interleaved DC-DC converters, such as Buck, Boost, or similar converter topologies, where multiple phases or interleaved stages are employed to improve efficiency, reduce ripple, or manage higher power levels. This flexibility makes the component 300 or 300’ suitable for a variety of power electronics applications requiring efficient magnetic coupling and phase isolation, thereby broadening its utility across numerous electrical power conversion systems. Its efficient design, low coupling, and minimal losses make it ideal for renewable energy systems, industrial motor drives, and consumer electronics. Although the disclosure has been described in terms of preferred embodiments as set forth above, it should be understood that these embodiments are illustrative only and that the claims are not limited to those embodiments. Those skilled in the art will be able to make modifications and alternatives in view of the disclosure, which are contemplated as falling within the scope of the appended claims. Non-exhaustive examples of the possible modifications and alternatives are described below. One potential alternative solution involves integrating grid-side filters, in addition to inverter-side filters. This approach could reduce noise, harmonics, and electromagnetic interference (EMI) while improving system efficiency, tailored specifically for power electronic systems connected to the grid. Furthermore, integrating both inverter and grid filters into a single component could provide additional benefits, such as reducing the total component count, simplifying the system design, and enabling high-density applications. This combined solution would also maintain low coupling coefficients, ensuring superior phase isolation and improving the quality of power conversion. For enhanced thermal management, alternative solutions could incorporate cooling systems, such as heat sinks or liquid cooling, directly into the magnetic component. This would lower operating temperatures, prevent heat-induced degradation, and extend the component’s operational life. Additionally, integrating magnetic shielding could significantly reduce EMI leakage, eliminating the need for separate shielding in the overall system design while maintaining a low coupling coefficient. While in the example represented by Figures 2 to 13, three inductors are integrated within the integrated magnetic component 300 or 300’, it would be understood that the integrated magnetic component 300 may integrate any suitable number / phase (i.e., two or more) of inductors. In particular, two or more magnetic circuits may be suitably stacked along the Z direction to integrate any suitable phases of inductors. It would be understood that in the case of a two-phase inductor, there will be only one common core section within the magnetic core. For more demanding applications, the solution could be adapted for multi-phase inverter systems, such as five-phase or six-phase inverters, where each phase has a dedicated magnetic component. This would improve system efficiency and power density by leveraging additional phases for better load balancing. Modular magnetic core designs could also allow for scalability and flexibility, adapting the system to a wide range of power and frequency requirements (from small electronics to large industrial applications) while ensuring low coupling between phases for optimal operation. For example, a five-phase inductor may be achieved by combining a three-phase integrated inductor (such as 300, 300’) and a two-phase integrated inductor, which act as basic building blocks for achieving any number of phases for multi-phase inverter systems. The number and size of air gaps in the winding columns 34A to 34C, 35A to 35C may be suitably adjusted based on operating conditions. This would optimize inductance and minimize winding and core losses across different load profiles. By modifying the air gap configuration, the magnetic field can be fine-tuned, ensuring optimal performance and minimizing energy loss, while maintaining low mutual coupling between phases. In some applications, the winding columns may not have any air gaps at all. Therefore, the number of air gaps within any given winding column may be expanded from 3 to m, where m is an integer equal to or greater than 0. Consequently, the number of split cores within any given winding column may be expanded from 4 to n, where n is an integer equal to or greater than 1. In other words, each winding column may be a single, continuous, core, or may comprise any suitable number of split cores.The number of split cores within a winding column is not limited to four, and can be suitably varied based upon particular applications. One or more of the core sections 30, 31, 32, and 33 may be constructed as a multilayered laminate structure using more than one magnetic material. The shapes of the winding columns and the shapes of the core sections, as shown in Figures 2 to 13, are just exemplary. Alternative shapes are possible. For example, the winding columns 34A to 34C and 35A to 35C may have any suitable cross-sectional shapes (e.g., circular, rectangular, oval, etc.) along theXY plane, and the core sections 30 to 33 may have cross-sectional shapes of any suitable geometry along the XY plane. It would be appreciated that the windings as shown in Figures 8, 9, and 12 are just examples, and the windings 36A to 36C and 37A to 37C may be constructed in any suitable way. For example, various winding wire types, including but not limited to enameled solid wire, Litz wire, and copper foil, may be used. In the example of Figure 8, flat wires are used to form vertical windings. Alternative winding orientations, wire types and / or wire materials are possible. The winding positions for phases A and C are not restricted to their original placements on winding columns 34A and 35A for phase A, and winding columns 34C and 35C for phase C. Instead, the windings for phases A and C may be extended to wrap around the bottom core section 30 and the top core section 33, respectively. For phase B, there may be a single winding wrapped around either winding column 34B or 35B. Air gap(s) may exist within one or more of the core sections 30 and 33 to allow for fine-tuning of the magnetic flux. One or more phases may comprise more than two winding columns placed between a pair of upper and lower core sections. Further, or alternatively, for a given phase, more than two windings may be interconnected to collectively form an inductor. Figure 15 schematically illustrates the processing steps of a method for assembling an integrated magnetic component (e.g., the component 300 or 300’). At step S1, a first magnetic circuit (e.g., the core sections 30, 31 and the magnetic pillars 34A, 35A) and a second magnetic circuit (e.g., the core sections 31, 32 and the magnetic pillars 34B, 35B) are formed within a magnetic core (e.g., the core 310) of the integrated magnetic component. The first and second magnetic circuits share a common core section (e.g., the core section 31) and are arranged at different sides of the common core section. The second magnetic circuit comprises a magnetic pillar (e.g., the pillar 34B or 35B) attached to a surface of the common core section. At step S2, at least one first winding (e.g., the windings 36A and 37A) is operatively associated with the first magnetic circuit to form a first inductor (e.g., La). At step S3, at least one second winding (e.g., the windings 36B and 37B) is operatively associated with the second magnetic circuit to form a second inductor (e.g., Lb). The at least one second winding includes a winding (e.g., the winding 36B or 37B) wound around the magnetic pillar (e.g., the pillar 34B or 35B). It would be appreciated that steps S1 to S3 may take place according to a sequence different from the described sequence. For example, steps S2 and S3 may be performed during step S1. More specifically, the component 300 may be assembled by: attaching the lower surfaces of the magnetic pillars 34A, 35A to an upper surface of the core section 30 (e.g., by using adhesives); installing the windings 36A, 37A such that the windings 36A, 37A surround the pillars 34A, 35A, respectively; attaching the lower surface of the core section 31 to the upper surfaces of the magnetic pillars 34A, 35A, thereby completing the first magnetic circuit and the phase A inductor; attaching the lower surfaces of the magnetic pillars 34B, 35B to an upper surface of the core section 31; installing the windings 36B, 37B such that the windings 36B, 37B surround the pillars 34B, 35B, respectively; attaching the lower surface of the core section 32 to upper surfaces of the magnetic pillars 34B, 35B, thereby completing the second magnetic circuit and the phase B inductor; attaching the lower surfaces of the magnetic pillars 34C, 35C to the upper surface of the core section 32; installing the windings 36C, 37C such that the windings 36C, 37C surround the pillars 34C, 35C, respectively; attaching the lower surface of the core section 33 to the upper surfaces of the magnetic pillars 34C, 35C, thereby completing the third magnetic circuit and the phase C inductor. The terms “having”, “containing”, “including”, “comprising” and the like are open and the terms indicate the presence of stated structures, elements or features but do not preclude the presence of additional elements or features. The articles “a”, “an” and “the” are intended to include the plural as well as the singular, unless the context clearly indicates otherwise. The skilled person will understand that in the preceding description and appended 5 claims, positional terms such as ‘upper’, ‘lower’, ‘clockwise’, ‘anticlockwise’ and ‘top’, ‘bottom’ etc., are made with reference to conceptual illustrations of an integrated inductor, such as that shown in the appended drawings. These terms are used for ease of reference but are not intended to be of a limiting nature. These terms are therefore to be understood as referring to an integrated inductor when in an orientation as shown in 10 the accompanying drawings. Each feature disclosed or illustrated in the present specification may be incorporated in the disclosure, whether alone or in any appropriate combination with any other feature disclosed or illustrated herein. 15

Claims

:

1. An integrated magnetic component comprising:a magnetic core comprising: a first magnetic circuit and a second magnetic circuit5 which share a common core section, wherein the first and second magnetic circuits are arranged at different sides of the common core section, and the second magnetic circuit comprises a magnetic pillar attached to a surface of the common core section;at least one first winding operatively associated with the first magnetic circuit to form a first inductor; and10 at least one second winding operatively associated with the second magneticcircuit to form a second inductor, wherein the at least one second winding comprises a winding wound around the magnetic pillar;wherein the magnetic pillar comprises one or more air gaps which divide the magnetic pillar into a plurality of split pillars, the plurality of split pillars being arranged 15 along a direction which is substantially perpendicular to the surface of the common core section.

2. The integrated magnetic component of claim 1, wherein the first and second magnetic circuits are stacked with one another along the direction which is substantially 20 perpendicular to the surface of the common core section.

3. The integrated magnetic component of claim 1 or 2, wherein, when viewed along the direction perpendicular to the surface of the common core section, the first and / or second magnetic circuit remains completely within a boundary of the common core 25 section.

4. The integrated magnetic component of any preceding claim, wherein the common core section comprises a magnetic material which has a higher magnetic permeability than a magnetic material of the magnetic pillar.

305. The integrated magnetic component of claim 4, wherein the magnetic permeability of the magnetic material of the common core section is more than five times higher than the magnetic permeability of the magnetic material of the magnetic pillar.08 12 256. The integrated magnetic component of any preceding claim, wherein the common core section comprises a magnetic material with a relative magnetic permeability of at least 500.5 7. The integrated magnetic component of any preceding claim, wherein thecommon core section is free from any air gap.

8. The integrated magnetic component of any preceding claim, further comprising one or more layers of non-magnetic material(s) arranged within the one or more air gaps.

109. The integrated magnetic component of any preceding claim, wherein the magnetic pillar comprises a magnetic material with a relative magnetic permeability of no greater than 250.15 10. The integrated magnetic component of any preceding claim, wherein each of thefirst and second magnetic circuits is a closed-loop magnetic circuit.

11. The integrated magnetic component of any preceding claim, wherein the surface of the common core section is a second surface and faces the at least one second20 winding, and the common core section further comprises a first surface that faces the at least one first winding.

12. The integrated magnetic component of claim 11, wherein:the first magnetic circuit comprises a first magnetic pillar and a second magnetic 25 pillar, both attached to the first surface of the common core section;the first magnetic circuit and the at least one first winding are configured such that a current flowing through the first inductor generates magnetic flux along a first direction within the first magnetic pillar and generates magnetic flux along a second direction within the second magnetic pillar; and30 the first and second directions are opposite to one another.

13. The integrated magnetic component of claim 12, wherein the at least one firstwinding comprises a first winding wound around the first magnetic pillar and a second winding wound around the second magnetic pillar.3508 12 2514. The integrated magnetic component of any one of claims 11 to 13, wherein:the magnetic pillar of the second magnetic circuit is a third magnetic pillar, and the second magnetic circuit further comprises a fourth magnetic pillar attached to the second surface of the common core section;5 the second magnetic circuit and the at least one second winding are configuredsuch that a current flowing through the second inductor generates magnetic flux along a third direction within the third magnetic pillar and generates magnetic flux along a fourth direction within the fourth magnetic pillar; andthe third and fourth directions are opposite to one another.1015. The integrated magnetic component of claim 14, wherein the winding of the at least one second winding is a third winding wound around the third magnetic pillar, and the at least one second winding further comprises a fourth winding wound around the fourth magnetic pillar.1516. The integrated magnetic component of claim 14 or 15 as dependent from claim 12, wherein: when viewed along the direction perpendicular to the surface of the common core section, the first magnetic pillar is generally aligned with one of the third and fourth magnetic pillars and the second magnetic pillar is generally aligned with the other of the 20 third and fourth magnetic pillars.

17. The integrated magnetic component of any preceding claim as dependent from claim 12, wherein the first magnetic circuit further comprises a first core section connecting the first magnetic pillar and the second magnetic pillar, and the first core 25 section is located at an end of the magnetic core along the direction perpendicular to the surface of the common core section.

18. The integrated magnetic component of claim 17, wherein the first core section comprises a magnetic material with a relative magnetic permeability of no greater than 30 150.

19. The integrated magnetic component of any preceding claim, wherein:the common core section is a first common core section, and the magnetic core further comprises a third magnetic circuit which shares a second common core section 35 with the second magnetic circuit;08 12 25the second and third magnetic circuits are arranged at different sides of the second common core section; andthe integrated magnetic component further comprises at least one third winding operatively associated with the third magnetic circuit to form a third inductor.

520. The integrated magnetic component of claim 19, wherein each of the first, second and third inductors is a standalone inductor.

21. A system comprising:10 a power conversion circuit comprising a plurality of AC phases, wherein theplurality of AC phases comprise a first AC phase and a second AC phase; andan integrated magnetic component according to any preceding claim, wherein the first inductor of the integrated magnetic component is electrically coupled to the first AC phase, and the second inductor of the integrated magnetic component is electrically15 coupled to the second AC phase.

22. The system of claim 21, wherein the system is configured such that, during operation of the system:a first electrical current flows between the first AC phase and the first inductor20 and a second electrical current flows between the second AC phase and the second inductor;the first electrical current generates a first magnetic flux within the first magnetic circuit, and the first magnetic flux flows through the common core section along a fifth direction;25 the second electrical current generates a second magnetic flux within the secondmagnetic circuit, and the second magnetic flux flows through the common core section along a sixth direction;when the first and second electrical currents are of the same polarity, the fifth direction is the same as the sixth direction.3023. The system of claim 22, wherein a phase difference between the first electrical current and the second electrical current is 360 / N, with N being a total number of the AC phases of the power conversion circuit.35 24. A method of assembling an integrated magnetic component, comprising:08 12 25forming a first magnetic circuit and a second magnetic circuit within a magnetic core of the integrated magnetic component, wherein the first and second magnetic circuits share a common core section and are arranged at different sides of the common core section, and wherein the second magnetic circuit comprises a magnetic pillar5 attached to a surface of the common core section;operatively associating at least one first winding with the first magnetic circuit to form a first inductor; andoperatively associating at least one second winding with the second magnetic circuit to form a second inductor, wherein the at least one second winding comprises a10 winding wound around the magnetic pillar;wherein the magnetic pillar comprises one or more air gaps which divide the magnetic pillar into a plurality of split pillars, the plurality of split pillars being arranged along a direction which is substantially perpendicular to the surface of the common core section.15s

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