Power transmission systems and methods

Abstract

The system and associated method transmit power between a DC power source and a variable load. Two power signals are extracted from the DC power source at HF ​​frequencies via two self-synchronous high-frequency rectifiers / amplifiers, which are switched by two corresponding HF switching signals with a phase difference controlled by a duty cycle and overlap controller. The two HF power signals are mixed in a wired, wireless, or bimodal wireless HF power link system to generate a transferred power signal based on the mixing and phase difference operations. The unfolded output power signal is generated from the transferred power signals by a power signal conversion circuit that communicates with the HF power link system. This system and method allows for the transfer of a phase-locked adjustable DC power signal and an AC power signal to at least one load, with the power signal already present in the load.

Description

Technical Field

[0001] Cross-reference This application claims the benefit of U.S. Patent Application No. 63 / 320,590, filed Mar. 16, 2022, and U.S. Application No. 63 / 476,781, filed Dec. 22, 2022, the contents of each of which are hereby incorporated herein by reference for all purposes.

[0002] The present invention relates to a power transmitter, a receiver, and a system and method for power transmission.

Background Art

[0003] In inductive power transfer (IPT), power is typically transferred between coils of wire by a magnetic field. An alternating current (AC) is driven through the transmitter coil to generate an oscillating magnetic field. The magnetic field passes through the receiver coil, where it induces an alternating current in the receiver coil. The induced alternating current either drives the load directly or is rectified to a direct current (DC) that is applied to drive the load. To achieve high efficiency, the transmitter coil and the receiver coil need to be very close to each other. For example, it is common for the transmitter coil and the receiver coil to be separated by only a fraction of the coil diameter (e.g., within centimeters) and for the axes of the coils to be closely aligned.

[0004] In some IPT systems, resonant inductive coupling is employed. Resonant inductive coupling can improve the efficiency of IPT by using resonant circuits. Resonant inductive coupling can achieve higher efficiency at longer distances than non-resonant inductive coupling. In resonant inductive coupling, power is transferred by a magnetic field between two resonant circuits (one on the transmitter side and one on the receiver side). These two circuits are tuned to resonate at the same resonant frequency.

[0005] In some IPT systems, the magnetic field can generate eddy currents in nearby metals. This can significantly increase the temperature and create a fire hazard. While ferrite plates may be used to provide shielding and improve inductive coupling, this can increase the cost of such systems.

[0006] Capacitive power transfer (CPT) utilizes an electric field to transfer power between two electrodes, such as metal plates. Typically, a CPT system uses four metal plates to form a capacitive coupler. Two plates act as power transmitters, while the other two function as power receivers, resulting in at least two coupling capacitors providing a power flow loop. An AC voltage is applied to the transmitting plates by the transmitters. The oscillating electric field induces an AC potential in the receiver plates, causing an AC current to flow into the load circuit. Resonance, in conjunction with capacitive coupling, can also extend the range of power transfer.

[0007] In CPT systems, eddy current losses can be reduced, and the plates used are low-cost, thus lowering the system cost. However, a problem with many systems is that high voltages can be applied to the plates. These high voltages can generate strong electric fields, resulting in large field emissions in the surrounding environment.

[0008] Furthermore, there are issues related to the capacitive or inductive compensation networks in CPT and IPT systems. Currently, both CPT and IPT systems require minimizing the isolation between the receiver and transmitter. This typically requires large capacitors and inductors in the primary and secondary compensation networks. These large components are difficult to manufacture, and parasitic resistance can significantly reduce system efficiency. Moreover, these compensation components do not directly participate in the power transmission process. [Overview of the project] [Problems that the invention aims to solve]

[0009] There is still a need for wireless power transmitters and receivers with fewer components and / or lower costs. There is still a need for wireless power transmitters and receivers with reduced reliance on compensation networks. There is still a need for highly efficient wireless power transmitters and receivers. There is still a need for wireless power transmitters with more flexible requirements regarding alignment and spacing. There is still a need for power transmission systems that can transmit power in both forward and reverse directions between loads and power sources, including between DC power sources and AC grids.

[0010] The field of power transmission related to consumer products is becoming increasingly important. In the automotive sector, electrical wire harnesses have become a critical and expensive subsystem of vehicles. The automotive wire harness market is expected to exceed US$77 billion in the next decade. In an era where fuel efficiency for internal combustion engine vehicles, carbon dioxide emissions for internal combustion engine vehicles, and driving range for electric vehicles are paramount, the cost, weight, and power transmission efficiency of these harnesses have become major concerns in vehicle design. This concern is perhaps understandable, considering that materials and components account for approximately 57% of the cost of manufacturing an automobile.

[0011] Battery technology is steadily improving to provide batteries with higher energy density, but at the same time, consumer demand is increasing for integrated, supplementary user electronic devices and electric drive systems in vehicles. This is leading to increasing demands on battery, vehicle weight, cost, and power transmission efficiency. In the 1990s, high-voltage battery systems were proposed for the automotive industry with the aim of reducing the weight of wire harnesses.

[0012] Much effort has been made to reduce the amount of expensive copper used in wire harnesses, and there is a movement toward using cheaper aluminum. This trend is also driven by the desire to save about 40 pounds of weight in a typical car. This trend toward aluminum has its own problems, partly because aluminum has a resistivity 1.58 times higher than copper. Aluminum also suffers from a phenomenon called creep, which causes connections to loosen. Furthermore, aluminum also oxidizes, so care must be taken when connecting it. Copper is still necessary in some aspects of wire harnesses, and connections between copper and aluminum cause galvanic potential problems.

[0013] It is clear that an alternative approach to vehicle wire harnesses is needed that reduces the expensive copper content, offers voltage flexibility, avoids the problems associated with aluminum, and reduces weight.

[0014] At the same time, just as development in the field of electric vehicles has accelerated, it is necessary to improve the efficiency of power transmission technology to keep up with rapidly advancing battery technology.

[0015] These requirements are not limited to the automotive sector; they are also relevant to fields such as solar energy power transmission, and, with some modifications, apply to other consumer electronics such as computer and television displays. While power regulating units that optimally extract power from various voltage sources are widely used today, their control systems are generally limited. This prevents the optimization of power transmission efficiency.

[0016] The aforementioned examples of the related technology and their associated limitations are for illustrative purposes only and are not intended to be exclusive. Further limitations of the related technology will become apparent to those skilled in the art by reading the specification and examining the drawings. [Means for solving the problem]

[0017] In a first embodiment, a bimodal short-range resonant wireless power transmission system is presented, configured to simultaneously perform capacitive and inductive power transmission according to an adjustable transmission mode ratio at a resonant power signal oscillation frequency, comprising: a transmitter subsystem comprising a transmitter antenna subsystem and a power signal tuner module, wherein the tuner module is configured to adjust the transmission mode ratio by adjusting the power signal supplied to the transmitter antenna subsystem by the tuner module; and a receiver subsystem comprising a receiver antenna subsystem configured to receive power from the transmitter antenna subsystem at the transmission mode ratio.

[0018] The tuner module may be configured to adjust the power signal by adjusting the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem. The transmitter subsystem may further include a controller and at least one sensor, the controller being configured to receive sensor information from at least one sensor and to automatically provide tuning commands to the tuner module based on the sensor information, and the tuner module being configured to adjust the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem in accordance with the tuning commands.

[0019] At least one sensor may be located on the transmitter subsystem. In other embodiments, at least one sensor may be located on the receiver subsystem, and the controller may be configured to receive sensor information wirelessly. The at least one sensor may be one of a power load sensor, a transmit power sensor, an ambient object detector, and a distance detector positioned to detect the distance between the transmitter antenna and the receiver antenna.

[0020] The resonant power signal oscillation frequency may vary freely within a predetermined frequency band. This predetermined frequency band may be the industrial, scientific, or medical (ISM) frequency band. The system may be detuned to such an extent that the resonant power signal oscillation frequency can vary within both ends of the predetermined frequency band.

[0021] In a further embodiment, a wireless method is provided for bimodal power transmission according to a transmission mode ratio adjustable at a resonant power signal oscillation frequency, comprising: a transmitter subsystem comprising a power signal tuner module and a transmitter antenna subsystem configured to resonate at a resonant power signal oscillation frequency; a receiver subsystem comprising a receiver antenna subsystem configured to resonate at a resonant power signal oscillation frequency; providing a power signal from the tuner module to the transmitter antenna subsystem at the power signal oscillation resonant frequency; adjusting the transmission mode ratio by adjusting the power signal from the tuner module to the transmitter antenna subsystem; and receiving the transmitted power at the power signal oscillation resonant frequency in the receiver subsystem via the receiver antenna subsystem at the transmission mode ratio. Adjusting the transmission mode ratio may include adjusting the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystem.

[0022] Providing a transmitter subsystem may further include providing a controller and at least one sensor, and adjusting the phase difference between current and voltage may be performed by a tuner module via a command from the controller, based on sensor information received by the controller from at least one sensor. The controller command may be automatically issued to the tuner module when the controller receives sensor information, and the tuner module may automatically execute the command from the controller to change the phase difference.

[0023] This method may further include enabling the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an industrial, scientific, and medical (ISM) frequency band. Providing the transmitter subsystem may include providing a transmitter subsystem that is detuned to an extent that the resonant power signal oscillation frequency can vary within both ends of the predetermined frequency band.

[0024] In a further aspect, there is provided a bimodal short-range resonant wireless power transfer system configured to simultaneously perform capacitive power transfer and inductive power transfer according to an adjustable transmission mode ratio of the capacitive power transfer to the inductive power transfer at a variable resonant power signal oscillation frequency, the system comprising: a transmitter subsystem comprising a transmitter antenna and a power signal tuner module, the power signal tuner module being configured to adjust the transmission mode ratio by adjusting a power signal provided to the transmitter antenna subsystem by the power signal tuner module; and a receiver subsystem comprising a receiver antenna subsystem configured to receive power from the transmitter antenna at the transmission mode ratio.

[0025] This system communicates information between the transmitter antenna subsystem and the receiver antenna subsystem via the transmitter antenna and the receiver antenna of the receiver antenna subsystem. This system may further comprise a modulator for modulating the information into an information transmission signal and providing the information transmission signal to the transmitter antenna subsystem. This system may modulate the information into an information transmission signal and provide the information transmission signal to the transmitter antenna subsystem. The modulator may be configured to modulate the information transmission signal to the transmitter antenna subsystem according to the information. The power signal tuner module may comprise a modulator.

[0026] The information transmission signal may have a frequency different from the variable resonance power signal oscillation frequency. The modulator may modulate the information transmission signal by any one of frequency modulation, amplitude modulation, and phase modulation. The information transmission signal may be modulated such that the variable power signal oscillation frequency is a harmonic of the frequency of the information transmission signal. The information transmission signal may be modulated to a harmonic of the power signal. The signal that is modulated and provided to the transmitter antenna subsystem may be a power signal.

[0027] The modulator may modulate the reflection characteristics of the receiver antenna and transmit information from the receiver antenna subsystem to the transmitter antenna subsystem by modulating the reflection characteristics of the receiver antenna according to the information. The modulated reflection characteristics of the receiver antenna may be the impedance of the receiver antenna.

[0028] This system may transmit information from the receiver subsystem to the transmitter subsystem by modulating the reflection of the signal from the transmitter subsystem by the receiver antenna. The receiver subsystem may modulate the reflection characteristics of the receiver antenna. The receiver subsystem may modulate the impedance of the receiver antenna.

[0029] A power load may exist at the output of the receiver subsystem, and the information may include one or more of the presence of the power load, the charge level of the power load, the power transmission efficiency, the charge rate of the power load, the state of the power load, the presence of the voltage applied to the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0030] This system may communicate digital information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. This system may communicate analog information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The receiver subsystem may be configured to transmit power to a subsequent receiver subsystem. The receiver may further include a rectifier with a phase shifter.

[0031] In a further embodiment, a bimodal resonant short-range high-frequency power transmission system is provided, comprising a plurality of power transceiver modules for simultaneously performing capacitive and inductive power transmission according to an adjustable transmission mode ratio via a power signal at a power signal frequency, wherein each of the plurality of power transceiver modules communicates via wire with a transmitter-receiver resonator arranged to exchange power with at least one other of the plurality of power transceiver modules.

[0032] A first of a plurality of power transceiver modules may include a power signal tuner module that is adjustable to change the transmission mode ratio by adjusting the power signal supplied by a power signal tuner module to a transmitter-receiver resonator that communicates via a wire with the first of the plurality of power transceiver modules. At least one of the plurality of power transceiver modules may include a modulator configured to modulate information into a high-frequency signal exchanged between an associated transmitter-receiver resonator that communicates via a wire with at least one of the plurality of power transceiver modules and a transmitter-receiver resonator that communicates via a wire with any of the other of the plurality of power transceiver modules.

[0033] The modulator may be an amplitude modulator, a frequency modulator, or a phase modulator. The information may include either or both digital and analog information. The high-frequency signal modulated by the modulator may be a power signal. The high-frequency signal modulated by the modulator may have a frequency different from the power signal frequency. The high-frequency signal modulated by the modulator may have a frequency that is a harmonic of the power signal frequency. The power signal frequency may be a harmonic of the frequency of the modulated signal.

[0034] A modulator may be configured to modulate the reflection characteristics of the associated wire-connected transmitter-receiver resonator according to the information, thereby imposing information on the signal reflected by the wire-connected transmitter-receiver resonator. A modulator may be configured to modulate the signal provided to the associated transmitter-receiver resonator according to the information. The power signal tuner module of the first of a plurality of power transceiver modules may include a modulator. Each of the power transceiver modules may include a compensation network, which may include a modulator. At least one of the power transceiver modules may include a high-frequency oscillator that provides a signal at a power signal frequency to at least one power transceiver module, which may include a modulator.

[0035] Each of the multiple power transceiver modules may be reconfigurable between a power transmitter mode and a power receiver mode. Each power transceiver module may include a differential self-synchronizing high-frequency power amplifier / rectifier that can be reconfigured between an amplifier state and a rectifier state corresponding to the power transmitter mode and power receiver mode of the power transceiver module, respectively. The differential self-synchronizing high-frequency power amplifier / rectifier may be a differential switch-mode self-synchronizing high-frequency power amplifier / rectifier. Each power transceiver module may include a controller, and the reconfiguration may be controlled by the controller. Each differential self-synchronizing high-frequency power amplifier / rectifier may include a phase shifter that can be adjusted by the controller to reconfigure the differential self-synchronizing high-frequency power amplifier / rectifier between an amplifier state and a rectifier state.

[0036] In receiver mode, if a power load is present at the output of one of several power transceiver modules, the information may include one or more of the following: the presence of the power load, the charge level of the power load, the power transmission efficiency, the charge rate of the power load, the state of the power load, the presence of a voltage applied to the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0037] In a further embodiment, a method is provided for short-range high-frequency transmission of power via a power signal at a power signal frequency, comprising providing a bimodal resonant short-range high-frequency power transmission system comprising a plurality of power transceiver modules, wherein each of the plurality of power transceiver modules communicates via wire with a transmitter-receiver resonator arranged to exchange power with at least one other of the plurality of power transceiver modules, and operating the power transmission system to perform capacitive and inductive power transmission simultaneously according to an adjustable transmission mode ratio.

[0038] The first of the multiple power transceiver modules provided may include a power signal tuner module, and operating the power transmission system may include changing the transmission mode ratio by adjusting the power signal tuner module. Providing a power transmission system may also include providing at least one of the multiple power transceiver modules that has a modulator and communicates via wire with an associated transmitter-receiver resonator, and operating the power transmission system may include exchanging high-frequency signals between the associated transmitter-receiver resonator and a transmitter-receiver resonator that communicates via wire with at least one other of the multiple power transceiver modules, and modulating the information into the exchanged high-frequency signals. If a power load is present at the output of one of the multiple power transceiver modules, the information may include, for example, one or more of the following, but are not limited to, the presence of the power load, the charge level of the power load, the power transmission efficiency, the charge rate of the power load, the state of the power load, the presence of a voltage applied to the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0039] The information may be modulated into a high-frequency signal to be exchanged by amplitude modulation, frequency modulation, or phase modulation. Modulating the information into a high-frequency signal to be exchanged may include modulating digital information or analog information into a high-frequency signal to be exchanged.

[0040] Modulating a high-frequency signal to which information is exchanged may include modulating the information into a power signal. Modulating a high-frequency signal to which information is exchanged may also include modulating the information into a signal having a frequency different from the power signal frequency. Modulating a high-frequency signal to which information is exchanged may also include modulating the information into a signal having a frequency that is a harmonic of the power signal frequency. Modulating a high-frequency signal to which information is exchanged may also include modulating the information as a harmonic into a signal having the power signal frequency.

[0041] Modulating a high-frequency signal on which information is exchanged may include, according to the information, modulating the reflection characteristics of the associated wire-connected transmitter-receiver resonator to impose the information on the signal reflected by the wire-connected transmitter-receiver resonator. Modulating a high-frequency signal on which information is exchanged may also include, according to the information, modulating the signal provided to the associated transmitter-receiver resonator.

[0042] This method may include operating a power signal tuner module of a first of a plurality of power transceiver modules to modulate a high-frequency signal to which information is exchanged. Each of the power transceiver modules provided may include a compensation network, which may include a modulator to operate the compensation network so that it can modulate a high-frequency signal to which information is exchanged. At least one of the power transceiver modules may include a high-frequency oscillator that provides a signal at a power signal frequency to at least one power transceiver module, which may include a modulator so that it can modulate in the oscillator a high-frequency signal to which information is exchanged.

[0043] Each of the multiple power transceiver modules provided may be reconfigurable between a power transmitter mode and a power receiver mode, and this method may further include reconfiguring at least two of the multiple power transceiver modules between a power transmitter mode and a power receiver mode to reverse the direction of power transmission between at least two transceiver modules. Each of the power transceiver modules provided may include a differential self-synchronizing high-frequency power amplifier / rectifier that can be reconfigured between an amplifier state and a rectifier state corresponding to the power transmitter mode and power receiver mode of the power transceiver module, and this method may include reconfiguring the differential self-synchronizing high-frequency power amplifier / rectifiers of at least two transceiver modules between an amplifier state and a rectifier state. Each differential self-synchronizing high-frequency power amplifier / rectifier may include an adjustable phase shifter for reconfiguring the differential self-synchronizing high-frequency power amplifier / rectifier between an amplifier state and a rectifier state, and this method may include adjusting the respective phase shifters of the differential self-synchronizing high-frequency power amplifier / rectifiers of at least two transceiver modules.

[0044] In a further embodiment, a short-range resonant wireless power transmission system is provided, comprising a transmitting subsystem comprising a plurality of substantially isolated transmitter resonators and corresponding transmitter modules that communicate power signals with each transmitter resonator, each transmitter module comprising a transmitting controller and a power signal source having a power signal oscillation frequency and a power signal phase, each power signal source being controlled by the corresponding transmitting controller; one or more receiver subsystems, each having a corresponding receiver resonator; a software lookup table of discrete allowable power signal oscillation frequencies of the power signal sources; and software loaded into memory and executed by the controller of one of the transmitter modules to perform an action, the action being to measure one of the input impedance of the corresponding transmitter resonator and the test signal power consumed by the corresponding transmitter resonator; and selecting a frequency from the lookup table for the corresponding power signal source based on one of the input impedance of the corresponding transmitter resonator and the test signal power consumed by the corresponding transmitter resonator. When executed, the software may perform actions to measure the level of power transmitted by the corresponding transmitter resonator while adjusting the phase of the power signal from the corresponding power signal source. The transmitter resonators may be substantially isolated from each other by an earth shield grid.

[0045] In a further embodiment, a wireless short-range method for transmitting power from a multi-transmitter subsystem to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency, comprising a multi-transmitter subsystem having a plurality of mutually independent transmitter resonators, each driven by a corresponding transmitter module that can be independently set to one of a plurality of preset power signal oscillation frequencies within a preset frequency band, and all transmitter resonators having a common transmitting surface; and a resonant receiver subsystem having a single receiver resonator overlapping with two or more of the transmitter resonators, positioned in close proximity to the common transmitting surface; and each input of the transmitter resonators A method is provided that includes measuring one of the impedance and the power consumed from the test signal by each of the transmitter resonators; setting the power signals to each of a plurality of mutually independent transmitter resonators to one of an off state and an active state based on one of the corresponding measured resonator input impedance and the power consumed from the test signal by the corresponding transmitter resonator; selecting a power signal oscillation frequency for each active transmitter resonator from a plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator; and setting the power signal for each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator to a phase that substantially maximizes power transmission through the transmitter resonator.

[0046] In a further embodiment, a wireless short-range method for transmitting power from a multi-transmitter subsystem to two or more resonant receiver subsystems at a variable resonant power signal oscillation frequency, comprising a multi-transmitter subsystem comprising a plurality of mutually independent transmitter resonators, each driven by a corresponding transmitter module that can be independently set to one of a plurality of preset power signal oscillation frequencies within a preset frequency band, and all transmitter resonators having a common transmitting surface; and arranging two or more resonant receiver subsystems, each having a single receiver resonator overlapping with two or more of the transmitter resonators, in close proximity to the common transmitting surface; and each of the transmitter resonators A method is provided that includes measuring one of the input impedance and the power consumed from the test signal by each of the transmitter resonators; setting the power signals to each of a plurality of mutually independent transmitter resonators to one of an off state and an active state based on one of the corresponding measured resonator input impedance and the power consumed from the test signal by the corresponding transmitter resonator; selecting a power signal oscillation frequency for each active transmitter resonator from a plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator; and setting the power signal for each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator to a phase that substantially maximizes power transmission through the transmitter resonator.

[0047] In a further embodiment, a short-range wireless system for transmitting power from a photocell to a power load is presented, comprising: a transmitting module that wire-communicates with a photocell and is configured to convert power from the photocell into an oscillating power signal having an oscillating frequency; a transmitter resonator that wire-communicates with the transmitting module and is configured to resonate at the oscillating frequency; a receiver resonator that is configured to resonate at the oscillating frequency and is arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; and a receiver module that wire-communicates with the receiver resonator and is configured to receive power from the receiver resonator and provide the received power in DC form to a power load via wire-communication.

[0048] The transmitting module may include a power amplifier configured to modulate the power received from the photocell at an oscillation frequency. The transmitting module may also include an oscillator configured to provide the oscillation frequency to the power amplifier. The transmitting module may also include a controller and one or more sensors, the controller configured to change the oscillation frequency based on first information from at least one of the one or more sensors. The transmitting module may also include a transmit tuning network configured, under the control of the controller, to change at least the phase of the power supplied by the transmitting module to the transmitter resonator based on second information from at least one of the one or more sensors.

[0049] The system may include a power adjustment unit electrically connected between the photocell and the transmitting module, and configured to adapt the power from the photocell to a format compatible with the transmitting module. The transmitting module may include small-signal electronics, and the power adjustment unit may be further configured to supply power to the small-signal electronics. The transmitter resonator may be located on the surface of the photocell facing the active solar radiation receiving surface of the battery. The transmitter resonator has a surface region having a range that is at least a majority of the range of the active solar radiation receiving surface of the battery.

[0050] The transmitter resonator may have a planar region smaller than that of the receiver resonator. The receiver resonator may be positioned and configured to receive power from a further transmitter resonator via at least one of capacitive coupling and magnetic induction at the resonant frequency.

[0051] In a further embodiment of a short-range wireless system for transmitting power from an array of photocells to a power load, the system comprises: a first plurality of transmitter modules, each transmitter module wire-communicating with a corresponding photocell in the array, and each transmitter module configured to convert power from the corresponding cell into an oscillating power signal having an oscillating frequency; a second plurality of transmitter resonators, each transmitter resonator wire-communicating with a corresponding transmitter module from the first plurality of transmitter modules and configured to resonate at an oscillating frequency; a single receiver resonator configured to resonate at an oscillating frequency and arranged to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a receiver module wire-communicating with the receiver resonator, configured to receive power from the receiver resonator and to provide the received power in DC form via wire-communicating to a power load.

[0052] Each of the first plurality of transmitting modules may include a power amplifier configured to modulate the power received from the corresponding photocell at an oscillation frequency. Each of the first plurality of transmitting modules may also include an oscillator configured to provide an oscillation frequency to the corresponding power amplifier. Each of the first plurality of transmitting modules may further include a controller and one or more sensors, the controller configured to change the oscillation frequency based on first information from at least one of the one or more sensors. Each of the first plurality of transmitting modules may also include a transmit tuning network configured, under the control of the corresponding controller, to change at least the phase of the power supplied by the transmitting module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors.

[0053] The system may include a third plurality of power adjustment units, each of which is electrically connected between the corresponding photocell and the corresponding transmitting module and configured to adapt the power from the corresponding photocell to a format compatible with the corresponding transmitting module. Each of the first plurality of transmitting modules may include a small-signal electronic circuit, and the corresponding power adjustment unit may be further configured to supply power to the small-signal electronic circuit. Each of the second plurality of transmitter resonators may be positioned on the surface of the corresponding photocell facing the active solar radiation receiving surface of the battery.

[0054] In a further embodiment of a short-range wireless system for transmitting power from an array of photocells to a power load, the system comprises: a first plurality of transmitter modules, each transmitter module configured to communicate via wired telecommunications with a corresponding photocell in the array, and each transmitter module configured to convert power from the corresponding cell into an oscillating power signal having an oscillating frequency; and a second plurality of transmitter resonators, each transmitter resonator configured to communicate via wired telecommunications with a corresponding transmitter module from the first plurality of transmitter modules and to resonate at the oscillating frequency. The system comprises a third plurality of receiver resonators, each of which is arranged to receive power from a corresponding transmitter resonator among a second plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each of which is configured to communicate via wired telecommunications with a corresponding receiver resonator among the third plurality of receiver resonators, to receive power from the corresponding receiver resonator, and to provide the received power in DC form to a power load via wired telecommunications.

[0055] Each of the first plurality of transmitting modules may include a power amplifier configured to modulate the power received from the corresponding photocell at an oscillation frequency. Each of the first plurality of transmitting modules may also include an oscillator configured to provide an oscillation frequency to the corresponding power amplifier. Each of the first plurality of transmitting modules may further include a controller and one or more sensors, the controller configured to change the oscillation frequency based on first information from at least one of the one or more sensors. Each of the first plurality of transmitting modules may also include a transmit tuning network configured, under the control of the corresponding controller, to change at least the phase of the power supplied by the transmitting module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors.

[0056] The system may further comprise a fifth plurality of power adjustment units, each of which is electrically connected between a corresponding photocell in the array of solar cells and a corresponding transmitting module in the first plurality of transmitting modules, and is configured to adapt the power from the corresponding photocell to a format compatible with the corresponding transmitting module. Each of the first plurality of transmitting modules may comprise a small-signal electronic circuit, and the corresponding power adjustment unit in the fifth plurality of power adjustment units may further be configured to supply power to the small-signal electronic circuit. Each of the second plurality of transmitter resonators may be positioned on the surface of a corresponding photocell in the array of solar cells, facing the active solar radiation receiving surface of the battery.

[0057] In a further embodiment, a short-range wireless system for transmitting power from an array of photocells to a power load, comprising: a first plurality of transmitting modules, each transmitting module configured to communicate via wired electrical communication with a corresponding photocell in the array, and each transmitting module configured to convert power from the corresponding cell into an oscillating power signal having an oscillating frequency; a second plurality of transmitter resonators, each transmitting resonator configured to communicate via wired electrical communication with a corresponding transmitting module from the first plurality of transmitting modules and to resonate at an oscillating frequency; and a smaller number of transmitter resonators than the plurality of transmitter resonators. A system is presented comprising: a third plurality of receiver resonators configured to resonate at an oscillation frequency, each of the third plurality of receiver resonators arranged to receive power from a portion of a plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each of which is configured to communicate via wired telecommunications with a corresponding receiver resonator, to receive power from the corresponding receiver resonator, and to provide the received power in DC form via wired telecommunications to a power load.

[0058] Each of the first plurality of transmitting modules may include a power amplifier configured to modulate the power received from the corresponding photocell at an oscillation frequency. Each of the first plurality of transmitting modules may also include an oscillator configured to provide an oscillation frequency to the corresponding power amplifier. Each of the first plurality of transmitting modules may further include a controller and one or more sensors, the controller configured to change the oscillation frequency based on first information from at least one of the one or more sensors. Each of the first plurality of transmitting modules may also include a transmit tuning network configured, under the control of the corresponding controller, to change at least the phase of the power supplied by the transmitting module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors.

[0059] The system may include a fifth or more power adjustment units, each of which is electrically connected between a corresponding photovoltaic cell in the array of solar cells and a corresponding transmitting module in the first or more transmitting modules, and is configured to convert the power from the corresponding photovoltaic cell into a format compatible with the corresponding transmitting module.

[0060] Each of the first plurality of transmitting modules may be equipped with a small-signal electronic circuit, and the corresponding power regulating unit of the fifth plurality of power regulating units may be further configured to supply power to the small-signal electronic circuit. Each of the second plurality of transmitting resonators may be positioned on the surface of the corresponding photocell of the solar cell array, facing the active solar radiation receiving surface of the battery.

[0061] In a further embodiment, a method is provided for transmitting power from a photocell to a power load, comprising: in a transmitting module, converting power from a photocell into an oscillating power signal having an oscillating frequency; transmitting power to a transmitter resonator configured to resonate at the oscillating frequency and to communicate with the transmitting module via a wired telecommunication; receiving power in a receiver resonator configured to resonate at the oscillating frequency and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving power in a receiver module communicating with the receiver resonator via a wired telecommunication; and providing the received power in DC form to a power load via wired telecommunication.

[0062] In a further embodiment of a method for transmitting power from a photocell array to a power load, the method includes: in each of a first plurality of corresponding transmitting modules, converting power from each of the photocells in the array into an oscillating power signal having an oscillating frequency; in each of the transmitting modules, transmitting power to a corresponding transmitter resonator among a second plurality of transmitter resonators, each configured to resonate at the oscillating frequency; receiving power in a receiver resonator configured to resonate at the oscillating frequency and arranged to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; receiving power in a receiver module that wire-communicates with the receiver resonator; and providing the received power in DC form to a power load via wire-communication.

[0063] In a further embodiment of a method for transmitting power from an array of photocells to a power load, the method includes: in each of a first plurality of corresponding transmitting modules, converting power from each photocell in the array into an oscillating power signal having an oscillating frequency; transmitting power from each of the transmitting modules to a corresponding transmitter resonator among a second plurality of transmitter resonators, each transmitter resonator being configured to resonate at the oscillating frequency; receiving power from each transmitter resonator in a corresponding receiver resonator configured to resonate at the oscillating frequency, each receiver resonator being further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving power from each receiver resonator in a corresponding receiver module that communicates with the receiver resonator via wired telecommunications; and providing the received power in DC form to a power load via wired telecommunications.

[0064] In a further embodiment of the method for transmitting power from an array of photocells to a power load, the method includes: in each of a first plurality of corresponding transmitting modules, converting power from each of the photocells in the array into an oscillating power signal having an oscillating frequency; transmitting power from each of the transmitting modules to a transmitter resonator of a second plurality of transmitter resonators, each transmitter resonator being configured to resonate at the oscillating frequency; receiving power from each transmitter resonator in any adjacent receiver resonator of a third plurality of receiver resonators configured to resonate at the oscillating frequency, each receiver resonator being further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; sharing the received power among the third plurality of receiver resonators; and providing the received power from one or more of the third plurality of receiver resonators in DC form via one or more corresponding receiver modules to a power load via wired telecommunications. This method may further include converting the voltage and current of the power from each photovoltaic cell to voltages and currents that are suitable for the corresponding transmitting module, before converting the power into an oscillating power signal.

[0065] A power transmission system for supplying power from a DC power source to a power load is provided, comprising: a high-frequency power amplifier configured to communicate with the power source via wired electrical communication and to convert a DC voltage from the power source into an AC voltage signal having an oscillation frequency; an adjustable phase high-frequency rectifier configured to receive power transmitted from the amplifier and to communicate with the power amplifier via wired electrical contact; and a receiver controller communicating with the rectifier, configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristics of the rectifier. The rectifier may be a differential self-synchronizing high-frequency rectifier.

[0066] The receiver controller may be configured to automatically adjust the current-voltage phase characteristics of the rectifier. The power transmission system may further include a load management system that communicates with the load via a wire, and is power-signally positioned between the load and the rectifier, and the load management system is configured to improve the efficiency of power transmission by adjusting the input impedance of the rectifier. The load management system may be configured to automatically adjust the current-voltage phase characteristics of the rectifier.

[0067] The power transmission system may further include a transmitter controller that communicates with the amplifier, and the transmitter controller is configured to improve the efficiency of power transmission by adjusting the current-voltage phase characteristics of the amplifier. The transmitter controller may also be configured to automatically adjust the current-voltage phase characteristics of the amplifier to improve the efficiency of power transmission.

[0068] The power transmission system may further include an oscillator that communicates with an amplifier and a transmitter controller. The transmitter controller may be configured to adjust the oscillation frequency via the oscillator.

[0069] The power amplifier may communicate directly via wired high-frequency communication with an adjustable phase high-frequency rectifier. The power amplifier may communicate wirelessly via short-range high-frequency communication with an adjustable phase high-frequency rectifier. The power transmission system may include a transmitter resonator that communicates via wired high-frequency communication with the power amplifier, and a receiver resonator that communicates via wired high-frequency communication with the rectifier. The transmitter resonator and the receiver resonator may communicate wirelessly via short-range high-frequency communication with each other. The power amplifier may perform at least one of capacitive short-range wireless high-frequency communication and inductive short-range wireless high-frequency communication with the rectifier. The power amplifier may communicate bimodal short-range wireless high-frequency communication with the rectifier.

[0070] The DC power supply may include a rechargeable battery, and the load may include an electric motor. The load may also include a computer monitor. The system's resonant structure may include at least one conductive mechanical load-bearing structural component of the system.

[0071] The system may further include a power adjustment unit electrically positioned between the power supply and the power transmission system, the power adjustment unit configured to adjust at least one of the current and voltage from the power supply to improve the efficiency of power transmission.

[0072] A method for power transmission from a DC power source to a power load is provided, which includes a power transmission system that communicates with the power source via a wired electrical connection, wherein the power transmission system comprises a high-frequency power amplifier that communicates with a power load via a wired electrical connection and an adjustable phase high-frequency rectifier, the method further comprising: in the amplifier, converting power from a DC power source into a high-frequency oscillating power signal; in the rectifier, converting the high-frequency oscillating power signal into a DC power signal; and adjusting the efficiency of power transmission by adjusting the current-voltage phase characteristics of the rectifier. Providing an adjustable phase high-frequency rectifier may include providing a differential self-synchronizing high-frequency rectifier.

[0073] This method may further include adjusting the efficiency of power transmission by adjusting the DC equivalent input resistance of the amplifier. Providing a power transmission system may also include providing a load management system that communicates via wire between the rectifier and the load. Adjusting the DC equivalent input resistance of the amplifier may include adjusting the input impedance of the rectifier by adjusting the load management system. Adjusting the load management system may include automatically adjusting the load management system.

[0074] This method may further include adjusting the efficiency of power transmission by adjusting the current-voltage phase characteristics of the power amplifier. Providing a power transmission system may also include providing a transmitter controller that communicates with the power amplifier to control it. Adjusting the current-voltage phase characteristics of the power amplifier may be performed by the transmitter controller. Adjusting the current-voltage phase characteristics of the power amplifier may be performed automatically by the transmitter controller.

[0075] This method may further include adjusting the efficiency of power transmission by changing the oscillation frequency of the power amplifier.

[0076] Providing a power transmission system may include providing a receiver controller that communicates with a rectifier to control the rectifier. Adjusting the current-voltage phase characteristics of the rectifier may be performed by the receiver controller. Adjusting the current-voltage phase characteristics of the rectifier may be performed automatically by the receiver controller.

[0077] Providing a power transmission system may include providing a power amplifier that communicates directly via wired high frequency with an adjustable phase high frequency rectifier. Providing a power transmission system may also include providing a power amplifier that communicates wirelessly via short-range high frequency with an adjustable phase high frequency rectifier.

[0078] Providing a power transmission system may include providing a transmitter resonator that communicates with a power amplifier via wired high-frequency communication, and a receiver resonator that communicates with a high-frequency rectifier via wired high-frequency communication. This method may further include operating the transmitter resonator and the receiver resonator with each other via wireless short-range high-frequency communication. Providing a power transmission system may also include providing a power amplifier that communicates with a rectifier via at least one of capacitive short-range wireless high-frequency communication and inductive short-range wireless high-frequency communication. Providing a power transmission system may also include providing a power amplifier that communicates with a rectifier via bimodal wireless short-range communication.

[0079] This method may further include providing a power regulating unit electrically positioned between a power source and a power transmission system, and adjusting the power regulating unit to adjust at least one of the current and voltage from the power source in order to improve the efficiency of power transmission.

[0080] A method for transmitting power from a DC power source to a power load, providing a power transmission system that communicates with the power source via wired telecommunications, wherein the power transmission system comprises an oscillator capable of oscillating at an oscillation frequency, a power amplifier and a transmitter tuning network both under the control of a transmitter controller, a receiver tuning network and a load management system both under the control of a receiver controller, the load management system communicating with a power load via wired telecommunications, and further providing a method comprising: in the power amplifier, converting power from the power source into an oscillating power signal having an oscillation frequency; transmitting the power signal from the power amplifier to the load management system via the transmitter tuning network and the receiver tuning network under the control of a transmitter controller; changing the power transmission speed by adjusting at least one of the oscillation frequency, the input DC equivalent resistance of the power amplifier, the transmitter tuning network, the receiver tuning network and the load management system; and providing the power received by the load management system to the power load in the form of DC via wired telecommunications.

[0081] Transmitting power signals via transmitter tuning networks and receiver tuning networks may include transmitting power by wired communication. Transmitting power signals via transmitter tuning networks and receiver tuning networks may also include transmitting power by wireless communication. Transmitting power by wireless communication may include transmitting power by short-range wireless communication. Transmitting power by short-range wireless communication may include transmitting power by at least one of capacitive coupling and inductive coupling.

[0082] Transmitting power from a DC power source may include transmitting power from at least one solar cell. Transmitting power from a DC power source may also include transmitting power from at least one solar cell battery. Transmitting power from a DC power source may also include transmitting power from power sources of various voltages.

[0083] In another embodiment, the electric system comprises a mechanical load-bearing structure having a conductive first portion, a power load, and a power transmission system comprising at least one high-frequency resonator configured for short-range wireless power transmission, wherein the resonator has at least a partially conductive first portion. The electric system may further comprise a rechargeable battery, and the power load may comprise an electric motor. The electric system may be an electric vehicle, and the mechanical load-bearing structure may include the vehicle's chassis. The electric system may be a display monitor, and the mechanical load-bearing structure may be at least one of the monitor's frame and base.

[0084] The electric system may further include a power supply. The power transmission system may include a high-frequency power amplifier configured to communicate with a power supply via wired electrical communication and to convert a DC voltage from the power supply into an AC voltage signal having an oscillating frequency; an adjustable phase high-frequency rectifier configured to receive power transmitted from the amplifier and to communicate with a power load via wired electrical contact and to communicate with the power amplifier via high frequency; and a receiver controller communicating with the rectifier configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristics of the rectifier.

[0085] In another embodiment, the device comprises a mechanical load-bearing structure having a conductive first portion; a power supply; a power load; a power transmission system comprising a high-frequency power amplifier configured to communicate with the power supply via wired electrical communication and to convert a DC voltage from the power supply into an AC voltage signal having an oscillating frequency; an adjustable phase high-frequency rectifier having wired electrical contact with the power load and communicating with the power amplifier via high frequency, wherein the rectifier is configured to receive power transmitted from the amplifier; and a receiver controller communicating with the rectifier, configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristics of the rectifier, wherein the conductive first portion is arranged to carry at least one high-frequency signal from the amplifier to the rectifier.

[0086] The device may further include a load management system positioned between the load and the rectifier, which communicates with the load via a wired power signal, and the load management system is configured to improve the efficiency of power transmission by adjusting the input impedance of the rectifier. The device may further include a transmitter controller that communicates with the amplifier, and the transmitter controller is configured to improve the efficiency of power transmission by adjusting the current-voltage phase characteristics of the amplifier. The device may further include an oscillator that communicates with the amplifier and the transmitter controller, and the transmitter controller is configured to adjust the oscillation frequency via the oscillator.

[0087] The power amplifier may communicate directly with the rectifier via a wired high-frequency communication via a conductive first portion. The power amplifier may communicate with the rectifier wirelessly via short-range high-frequency communication. The power transmission system may include a transmitter resonator communicating with the power amplifier via a wired high-frequency communication and a receiver resonator communicating with the rectifier via a wired high-frequency communication, and one of the transmitter resonator and the receiver resonator may include a conductive first portion. The transmitter resonator and the receiver resonator may communicate with each other wirelessly via short-range high-frequency communication. The power amplifier may perform at least one of capacitive short-range wireless high-frequency communication and inductive short-range wireless high-frequency communication with the rectifier. The power amplifier may communicate with the rectifier bimodal short-range wireless high-frequency communication. The DC power supply may include a rechargeable battery, and the load may include an electric motor.

[0088] In some embodiments, the sealed bidirectional power transmission circuit device comprises a plurality of terminals arranged for electrical communication with a device outside the sealed device, wherein the sealed device is a multi-terminal power switching device having at least one DC terminal, at least one AC terminal, and at least one control terminal, which is adjustable between an amplified state and a rectified state, and is configured to communicate bidirectionally with DC voltage and DC current via at least one DC terminal, and bidirectionally with a high-frequency power signal having amplitude, frequency, and phase via at least one AC terminal; and a phase, frequency, and duty cycle adjustment circuit which communicates wired data with a controller and wired electrical communication with the power switching device via at least one control terminal, which is configured to adjust the power switching device between an amplified state and a rectified state by establishing a high-frequency oscillation signal having the frequency and phase of a high-frequency power signal at at least one control terminal of the power switching device, and adjusting the phase of the high-frequency oscillation signal under the command of the controller. In some embodiments, the controller may be located inside the sealed device of the sealed bidirectional power transmission circuit device. Multiple terminals in a sealed power transmission circuit device may include terminals for data communication between the controller and an external device inside the seal.

[0089] The high-frequency power signal may have a duty cycle, and the phase, frequency, and duty cycle adjustment circuit may be further configured to adjust the duty cycle of the high-frequency power signal by adjusting the duty cycle of the high-frequency oscillation signal. The phase, frequency, and duty cycle adjustment circuit may include a high-frequency oscillator for generating the high-frequency oscillation signal under command from a controller.

[0090] The sealed power transmission circuit device may further include a tuning network within the encapsulation that communicates with a controller via wired data and with a power switching device via wired electrical communication through at least one AC terminal, the tuning network being configured to adjust a high-frequency power signal to a tuned high-frequency power signal under command from the controller. The bidirectional power transmission circuit device may include a modulator configured to modulate information into a high-frequency power signal. The modulator may include a tuning network. The modulator may be configured to modulate the high-frequency power signal with information provided by the controller. The tuning network may include a harmonic termination network circuit configured to suppress harmonics of the high-frequency oscillation signal in the high-frequency power signal. The harmonic termination network may include one or more inductors and one or more of a first harmonic termination, a second harmonic termination, and a third harmonic termination. The sealed power transmission circuit device may further include an amplitude / frequency / phase detector located within the encapsulation, which is arranged to communicate with a controller via wired data communication and with a tuning network via wired electrical communication, and which is arranged to determine the amplitude, frequency, and phase of any high-frequency power signal communicated between the tuning network and an external AC load / source of the sealed device. The tuning network may further include one or more of a compensation network, a matching network, and a filter.

[0091] Phase, frequency, and duty cycle adjustment circuits may be configured to receive commands from the controller based on measurement data communicated to the controller by the amplitude / frequency / phase detector. The phase, frequency, and duty cycle adjustment circuits may also be configured to adjust the high-frequency oscillation signal based on feedback signals received directly from the amplitude / frequency / phase detector. The tuning network may include a voltage-current tuner for adjusting the phase difference between the voltage and current of the tuned high-frequency power signal based on measurement data from the amplitude / frequency / phase detector when the power switching device is in an amplified state.

[0092] The sealed power transmission circuit device may further include a power management circuit configured within the encapsulation to wired electrical communication between the power switching device and an external DC power supply / load to match the impedance of the power switching device and the external DC power supply / load, and to adjust the DC power communicated between the power switching device and the DC power supply / load based on feedback signals received directly from amplitude / frequency / phase detectors. In other embodiments, the sealed power transmission circuit device may further include a power management circuit configured within the encapsulation to wired data communication with a controller and wired electrical communication between the power switching device and an external DC power supply / load to match the impedance of the power switching device and the external DC power supply / load, and to adjust the DC power communicated between the power switching device and the DC power supply / load based on measurement data communicated to the controller by amplitude / frequency / phase detectors.

[0093] The sealed power transmission circuit device may further include a voltage / current detector positioned within the encapsulation to determine the DC voltage and DC current passing between the power switching device and the power management circuit, in wired data communication with a controller. Phase, frequency, and duty cycle adjustment circuits may be configured to receive commands from the controller based on measurement data communicated to the controller by the voltage / current detector. In other embodiments, the phase, frequency, and duty cycle adjustment circuits may be configured to adjust the high-frequency oscillation signal based on feedback signals received directly from the voltage / current detector.

[0094] The sealed power transmission circuit device may further include a controller, an amplitude / frequency / phase detector, and a voltage / current detector, and a memory that communicates with them via wired data within the encapsulation. The memory is configured to receive and store measurement data from the two detectors and to provide signal data from the two detectors to the controller.

[0095] The sealed power transmission circuit device may further include a power management circuit configured within the encapsulation to communicate via wired electrical communication between the power switching device and an external AC power supply / load to match the amplitude, frequency, and phase of the power switching device with the external AC power supply / load, and to adjust the AC power communicated between the power switching device and the AC power supply / load based on feedback signals received directly from amplitude / frequency / phase detectors.

[0096] The sealed power transmission circuit device may further include a power management circuit configured within the encapsulation to communicate via wired data with a controller and via wired electrical communication between the power switching device and an external AC power supply / load to match the amplitude, frequency, and phase of the power switching device with the external AC power supply / load and the power switching device, and to adjust the AC power communicated between the power switching device and the AC power supply / load based on measurement data communicated to the controller by amplitude / frequency / phase detectors.

[0097] The sealed power transmission circuit device may further include a voltage / current detector located inside the encapsulation, which communicates via wired data with a controller to determine the DC voltage and DC current passing between the power switching device and the power management circuit.

[0098] In some embodiments, the phase, frequency, and duty cycle adjustment circuits are configured to receive commands from the controller based on measurement data communicated to the controller by the voltage / current detector. In some embodiments, the phase, frequency, and duty cycle adjustment circuits are configured to adjust the high-frequency oscillation signal based on feedback signals received directly from the voltage / current detector.

[0099] The sealed power transmission circuit device may further include a controller, an amplitude / frequency / phase detector, and a voltage / current detector, and a memory that communicates with them via wired data within the encapsulation. The memory is configured to receive and store measurement data from the two detectors and to provide signal data from the two detectors to the controller.

[0100] The sealed power transmission circuit device may further include, within its encapsulation, at least one of the following: a Bluetooth communication circuit, a WiFi communication circuit, a Zigbee communication circuit, and a cellular communication technology circuit, for communicating information between the controller and a device outside the sealed power transmission circuit device. The communication circuit may communicate bidirectionally via a wired connection with at least one communication antenna configured to communicate with a device outside the sealed power transmission circuit device. The antenna for the communication circuit may be located within the encapsulation of the sealed device.

[0101] A bidirectional power transmission circuit device may include a modulator configured to modulate information into at least one of a high-frequency power signal and a DC voltage. The modulator may include a power switching device. The modulator may be configured to modulate at least one of a high-frequency power signal and a DC voltage with information provided by a controller. The modulator may further include phase, frequency, and duty cycle adjustment circuits.

[0102] In some embodiments, all circuit elements of a bidirectional power transmission circuit device may be monolithically integrated on a silicon single-crystal wafer. In some embodiments, at least a portion of the circuit elements of the device may be integrated by flip-chip technology.

[0103] In one particular embodiment, the electronics of a sealed bidirectional power transmission circuit device may be mounted on a single silicon single-crystal wafer, along with at least one photocell that functions as a DC source / load. In a further embodiment, the electronics of a sealed bidirectional power transmission circuit device may be mounted on the surface of a single silicon single-crystal wafer, along with at least one photocell that functions as a DC source / load and a resonator structure that functions as an AC load / source. Antennas used in Bluetooth, WiFi, Zigbee, and cellular technologies may also be integrated on the same single silicon single-crystal wafer.

[0104] In another embodiment, a power transmission system is provided for transmitting power between a DC power supply and a variable load. First and second self-synchronous high-frequency rectifiers / amplifiers are configured to extract first and second high-frequency (HF) power signals from the DC power supply at first and second HF frequencies, respectively. An HF power link system is configured to receive and mix the first and second HF power signals to generate a transferred power signal. A power signal conversion circuit communicating with the HF power link system and the variable load is configured to generate an output power signal from the transferred power signal and to supply that output power signal to the variable load.

[0105] The power transmission system further includes an HF switching signal generator configured to supply first and second switching signals at first and second HF frequencies to first and second rectifiers / amplifiers, respectively, and to establish and control the mutual phase relationship between the first and second switching signals.

[0106] The power signal conversion circuit includes a switch-mode rectifier configured to receive a power signal transferred from an HF power link system, rectify the transferred power signal, and generate a rectified power signal. The unfolding circuit is configured to receive the rectified power signal from the switch-mode rectifier, unfold the rectified power signal, and generate an output power signal.

[0107] The first and second self-synchronous high-frequency rectifiers / amplifiers can be configured to operate in rectification mode, and the switch-mode rectifier can be configured to operate in always-on mode, thereby allowing power to be extracted from the variable power input to the load and transmitted to the DC power supply via a power signal conversion circuit and an HF power link system.

[0108] An unfolding circuit may be configured to receive a reference signal from a variable load and unfold a rectified power signal synchronized with the signal in the variable load. A power signal conversion circuit, an HF power link system, and multiple pairs of self-synchronous high-frequency rectifiers / amplifiers may be configured to communicate control information from the rest of the system to an HF switching signal generator. The system may further include one or more controllers configured to communicate data with and control multiple elements of the system. The system may further include an isolated load information circuit configured to communicate information to the HF switching signal generator regarding at least one of the DC level, frequency, and phase of the power signal in the variable load. The load information circuit may include a phase-locked loop. The load information circuit may further include an isolator system which may include an air gap. The HF power link system may include a wireless power link system, which may be a bimodal wireless HF power link system. The HF power link system may also include a wired power link system.

[0109] In the two phase-difference-based implementations, the first and second HF frequencies are the same. The first and second switching signals may have a relative phase difference that can be adjusted by an HF switching signal generator. In the first phase-difference-based implementation, the HF switching signal generator is configured to adjust the relative phase difference between the first and second switching signals based on the DC level of a variable load, thereby generating a power signal transmitted from the HF power link system as a DC signal with correspondingly adjusted amplitude. In the second phase-difference-based implementation, the HF switching signal generator modulates the relative phase difference between the first and second switching signals with a phase modulation frequency derived from the frequency of the power signal at the variable load, thereby generating a power signal that is transmitted from the HF power link system as an AC power signal modulated at the frequency of the power signal at the variable load.

[0110] In a frequency difference-based implementation, the first and second HF frequencies differ by a difference frequency Δf. In this embodiment, the HF switching signal generator is configured to determine the first and second HF frequencies and set the difference frequency Δf to double the frequency of the power signal at the variable load. The HF power link system is configured to generate a transmission power signal at the difference frequency Δf, and the power signal conversion circuit is configured to supply an output power signal to the variable load at the frequency of the power signal at the variable load.

[0111] In a further embodiment, a method is provided for transmitting power between a DC power source and a variable load, the method comprising: extracting corresponding first and second HF power signals from a DC power source at first and second high-frequency (HF) frequencies via corresponding first and second self-synchronous high-frequency rectifiers / amplifiers; receiving and mixing the first and second HF power signals in an HF power link system to generate a transferred power signal; generating an output power signal in a power signal conversion circuit communicating with the HF power link system and a variable load, based at least in part on the transferred power signal; and supplying the output power signal to the variable load.

[0112] The method may further include the steps of generating first and second switching signals at first and second frequencies, respectively, in an HF switching signal generator that communicates with the first and second rectifiers / amplifiers, and establishing and controlling the mutual phase relationship between the first and second switching signals in the HF switching signal generator. The method may further include the steps of receiving and rectifying the power signal transferred from the HF power link system in a switch-mode rectifier of the power signal conversion circuit, and receiving and unfolding the power signal rectified from the switch-mode rectifier in an unfolding circuit of the power signal conversion circuit. The method may further include the steps of setting the first and second self-synchronous high-frequency rectifiers / amplifiers to rectification mode, setting the switch-mode rectifier to always-on mode, extracting power from the variable load, and transferring the extracted power to the DC power supply via the power signal conversion circuit and the HF power link system.

[0113] The method includes the steps of: developing a rectified power signal synchronized with the signal in the variable load based on a reference signal from the variable load; communicating control information from the rest of the system to an HF switching signal generator via a power signal conversion circuit, an HF power link system, and first and second self-synchronous high-frequency rectifiers / amplifiers; controlling multiple elements of the system by one or more controllers that communicate data with multiple elements; and communicating information regarding at least one of the DC level, frequency, and phase of the power signal in the variable load to the HF switching signal generator using an isolated load information circuit including a phase-locked loop and an optional isolator system. Power signal transfer in the HF power link system may include wireless, bimodal wireless, or wired power signal transfer.

[0114] Two methods for transmitting power from a DC power source to a variable load utilize the phase difference between switching signals. In these methods, the first and second switching signals have the same frequency and a phase difference between them that can be adjusted by an HF switching signal generator. The first method of these examples includes adjusting the phase difference between the first and second switching signals based on the DC level of the variable load to generate the power signal transmitted from the HF power link system as a DC signal with correspondingly adjusted amplitude. The second method of these implementations further includes modulating the phase difference between the first and second switching signals with a phase modulation frequency derived from the frequency of the power signal of the variable load to generate the power signal transmitted from the HF power link system as an AC power signal modulated at the frequency of the power signal of the variable load.

[0115] A frequency difference-based method further includes the steps of determining the first and second frequencies in each pair of corresponding first and second switching signals, and setting the difference frequency of each pair to twice the frequency of the power signal of the variable load. This method further includes the steps of generating a power signal transmitted at the difference frequency from the HF power link system, and supplying an output power signal to the variable load at the frequency of the power signal in the variable load.

[0116] The power transmission systems described herein can utilize either a phase difference or a frequency difference between switching signals supplied to a pair of self-synchronous high-frequency rectifiers / amplifiers to transmit either AC power or DC power from a DC power source to a variable load. This can also be extended to transmit power from a single DC power source to a single variable load via multiple rectifier / amplifier pairs, or to transmit power from multiple DC power sources to a single variable load using multiple rectifier / amplifier pairs. Apparatus and methods for achieving these objectives are described. These apparatuses and methods, in some implementations, also enable the simultaneous transmission of DC and AC power to the load.

[0117] In one embodiment, a solar panel system for generating and transmitting power to an AC load is provided. The system comprises at least one solar cell having a planar photosensitive surface facing a solar cover, arranged on the surface of a first solar cover, a high-frequency power module corresponding to each solar cell, a printed circuit board supported on a flat surface of the printed circuit board opposite the solar cover, a high-frequency power circuit for wired telecommunications, and at least one corresponding solar cell; a conformal encapsulation layer coupled to the first plane of the solar cover and covering at least one solar cell and the corresponding high-frequency power module, and a frame carrying a single aggregator for receiving power from at least one high-frequency power circuit and transmitting power to an AC load at the AC load line frequency.

[0118] The high-frequency power circuits may be located on a flat surface of a printed circuit board opposite the solar cover. At least one planar printed circuit board may be located adjacent to at least one corresponding photocell. At least one photocell may be arranged in an array. All high-frequency power circuits may be phase-locked to each other. All high-frequency power circuits can be phase-locked to each other to the AC power signal of an AC load via a phase-locked loop.

[0119] In some embodiments, the aggregator may be configured to receive power from at least one high-frequency power circuit by wireless power transmission. The aggregator may be configured to receive power from at least one high-frequency power circuit by bimodal wireless power transmission. Each of the high-frequency power circuits may include a transmitter resonator configured to receive power from at least one corresponding solar cell. The system may include a receiver resonator configured to receive power from the transmitter resonator. The aggregator may include a low-frequency unfolding circuit, a switch-mode rectifier, and a receiver module configured to receive power from the receiver resonator by wired communication. The receiver resonator may be frame-mounted. The aggregator may be mounted on the receiver resonator.

[0120] In some embodiments, the aggregator may be configured to receive power from at least one high-frequency power circuit by wired power transmission at low frequency. Each high-frequency power circuit includes a transmitter module configured to receive power from at least one corresponding solar cell, a receiver module that wires with the transmitter module and receives power from the transmitter module at high frequency, and a switch-mode rectifier that generates a low-frequency power signal. The aggregator may include an unfolding circuit that can receive power at low frequency from the high-frequency power circuit and transmit that power to an AC load at the AC load line frequency.

[0121] The first solar cover surface may include an optically transparent polymer layer. This system may be equipped with a dielectric protective cap on the high-frequency power circuit. The protective cap may be positioned above or below the conformal encapsulation layer. The periphery of the protective cap may be positioned below the conformal encapsulation layer and sealed to the conformal encapsulation layer.

[0122] A method for manufacturing a solar panel is provided, the method comprising the steps of: arranging at least one solar cell having a photosensitive surface facing the surface of a transparent solar cover on a flat surface of the transparent solar cover; and comprising the steps of: providing a high frequency; a power module comprising a high frequency power circuit on a printed circuit board that wires to the at least one solar cell in order to collect power from the at least one solar cell, wherein the high frequency power circuit is arranged on the plane of the printed circuit board; the board facing the opposite side of the transparent solar cover; arranging a heat-deformable polymer sheet extending across the surface area of ​​the transparent solar cover on the opposite side of the at least one solar cell from the transparent solar cover to form a laminated stack in a plane; transferring the laminated stack to a vacuum oven and vacuuming the inside of the vacuum oven to remove the air between the layers of the laminated stack; heating the laminated stack to the deformation temperature of the heat-deformable polymer sheet; and applying pressure to the stack perpendicular to the plane. The process involves restoring ambient pressure in a vacuum oven, bonding a heat-deformable polymer sheet onto a transparent solar cover, pressing the heat-deformable polymer sheet equiangled onto at least one solar cell and a high-frequency power module to form a packaged solar cell array; and mounting the array of packaged solar cell modules onto a frame.

[0123] The method may further include the step of placing a transparent thermocrosslinkable polymer sheet on a transparent solar cover before placing at least one solar cell and a high-frequency power module on the transparent solar cover. Placing a thermocrosslinkable polymer sheet may include placing a thermocrosslinkable polymer sheet. The step of placing a thermocrosslinkable polymer sheet may include one or more layers of polyethylene terephthalate, biaxially oriented polyethylene terephthalate, ethylene vinyl acetate; fluoropolyester; polyvinyl fluoride; polyvinylidene fluoride; polyethylene vinyl acetate; polyethylene naphthalate; ethylene tetrafluoroethylene; fluoroethylene vinyl ether; tetrafluoroethylene-hexafluoropropylene-vinylidene fluoride copolymer; polyamide; polypropylene; polyethylene; polyvinylidene fluoride - sugar palm short fibers.

[0124] Mounting a packaged array of photovoltaic modules to a frame may include mounting the packaged array of photovoltaic modules to a frame that supports a receiver resonator and an aggregator configured to receive power signals from a high-frequency power circuit via the receiver resonator. Mounting a packaged array of photovoltaic modules to a frame may include mounting the packaged array of photovoltaic modules to a frame that supports an aggregator configured to receive power signals from a high-frequency power circuit via a wire.

[0125] When considering a solar panel system without regard to the packaging of the solar power modules, it can be described as a solar panel system for generating and transmitting power to an AC load. A high-frequency power module corresponding to each solar cell communicates via wired telecommunications with at least one corresponding solar cell. The frame carries a single aggregator, which is configured to receive power from at least one high-frequency power module and transmit power to an AC load at the AC load line frequency. All at least one high-frequency power module can phase-lock with each other to the AC power signal at the AC load via a phase-locked loop. Each of the at least one high-frequency power module may include an HF switching signal generator that can phase-lock with the power signal of the AC load having the AC load line frequency, and first and second high-frequency switch-mode power rectifiers / amplifiers powered by power supplied from the corresponding at least one solar cell. The solar cells correspond to first and second high-frequency power signals whose frequencies differ by an amount equal to twice the AC load line frequency. The aggregator of the solar panel system may include an unfolding circuit configured to receive transmitted power supplied from each of at least one solar cell at a frequency twice the AC load line frequency.

[0126] In some embodiments, the aggregator of the solar panel system is configured to receive power from at least one high-frequency power module via wireless power transmission.

[0127] In some embodiments, the aggregator of the solar panel system is arranged to receive power from at least one high-frequency power module by bimodal radio power transmission. In these embodiments, each high-frequency power module comprises a transmitter resonator that wires to a transmitter module arranged to receive power from the corresponding at least one solar cell. The photovoltaic system also comprises a single receiver resonator arranged to receive power by bimodal power transmission from a transmitter resonator corresponding to at least one solar cell. The aggregator comprises a low-frequency unfolding circuit, a switch-mode rectifier, and a receiver module arranged to receive power from a receiver resonator by wired communication. The receiver resonator is frame-mounted, and the aggregator may be mounted to the receiver resonator.

[0128] In another embodiment, the aggregator of the solar panel system is configured to receive power from at least one high-frequency power module by low-frequency wired power transmission. Each high-frequency power module includes a transmitter module configured to receive power from at least one corresponding solar cell, a receiver module that communicates with the transmitter module via a wire and receives power from the transmitter module at high frequency, and a switch-mode rectifier that generates a low-frequency power signal. The aggregator includes an unfolding circuit that can receive power at low frequency from the high-frequency power module and transmit that power to an AC load at the AC load line frequency.

[0129] In another embodiment, each high-frequency power module comprises a transmitter module positioned to receive power from at least one corresponding solar cell, a receiver module that communicates via a wire with the transmitter module and receives power from the transmitter module at a high frequency, and a switch-mode rectifier that generates a low-frequency power signal. An unfolding circuit unfolds the low-frequency signal from the switch-mode rectifier. In this embodiment, the aggregator may simply be a device that collects all unfolding signals at the AC load line frequency from each of the unfolding circuits associated with each of the corresponding photocells. [Brief explanation of the drawing]

[0130] [Figure 1] This is a schematic diagram of a wireless power transmission system according to one exemplary embodiment. [Figure 2A] The antennas shown may be used in various exemplary embodiments, either by themselves or in combination with other disclosed elements. [Figure 2B] The antennas shown may be used in various exemplary embodiments, either by themselves or in combination with other disclosed elements. [Figure 2C] The antennas shown may be used in various exemplary embodiments, either by themselves or in combination with other disclosed elements. [Figure 3A] The following are side views of antennas that may be used in various exemplary embodiments, either by themselves or in combination with other disclosed elements. [Figure 3B] The following are side views of antennas that may be used in various exemplary embodiments, either by themselves or in combination with other disclosed elements. [Figure 4A] Side views of exemplary resonators that may be used in various exemplary embodiments, by themselves, or in combination with other disclosed elements are shown. [Figure 4B] Side views of exemplary resonators that may be used in various exemplary embodiments, by themselves, or in combination with other disclosed elements are shown. [Figure 4C] Side views of exemplary resonators that may be used in various exemplary embodiments, by themselves, or in combination with other disclosed elements are shown. [Figure 4D] Side views of exemplary resonators that may be used in various exemplary embodiments, by themselves, or in combination with other disclosed elements are shown. [Figure 5] Cross-sectional views of exemplary resonators that may be used in various exemplary embodiments, either by themselves or in combination with other disclosed elements are shown. [Figure 6] This is a schematic diagram of the primary side of a wireless power transmission system according to one exemplary embodiment. [Figure 7] This is a schematic diagram of the secondary side of a wireless power transmission system according to one exemplary embodiment. [Figure 8] This is a schematic diagram of an exemplary power amplifier that may be used in various exemplary embodiments, by itself, or in combination with other disclosed elements. [Figure 9] This is a schematic diagram of an exemplary self-synchronizing rectifier that may be used in various exemplary embodiments, by itself, or in combination with other disclosed elements. [Figure 10] A more detailed schematic diagram of the V / I tuner shown in Figure 6 is used to adjust the power signal to the transmitter resonator according to one embodiment. [Figure 11] A flowchart of a short-range resonant wireless method for bimodal power transmission according to a transmission mode ratio adjustable at the resonant power signal oscillation frequency is shown, according to one exemplary embodiment. [Figure 12] This is a schematic diagram of a multi-transmitter short-range resonant wireless power transmission system for transmitting power to a single receiver subsystem. [Figure 13A] This describes a multi-transmitter short-range resonant wireless power transmission system for transmitting power to a single receiver subsystem. [Figure 13B] This describes a multi-transmitter short-range resonant wireless power transmission system for transmitting power to a single receiver subsystem. [Figure 14] This document describes a multi-transmitter short-range resonant wireless power transmission system for transmitting power to one or more receiver subsystems. [Figure 15] A flowchart shows a wireless short-range method for transmitting power from a multi-transmitter subsystem to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency. [Figure 16] A flowchart shows another wireless short-range method for transmitting power from a multi-transmitter subsystem to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency. [Figure 17] A flowchart shows a wireless short-range method for transmitting power from a multi-transmitter subsystem to one or more resonant receiver subsystems at a variable resonant power signal oscillation frequency. [Figure 18] A flowchart shows another wireless short-range method for transmitting power from a multi-transmitter subsystem to one or more resonant receiver subsystems at a variable resonant power signal oscillation frequency. [Figure 19A] This document describes a short-range resonant wireless power transmission system for wirelessly transmitting power from a photovoltaic solar cell to a power load. [Figure 19B] This shows a power transmission system for transmitting power from a photovoltaic solar cell to a power load. [Figure 20A] Figure 19A shows a front view of a solar cell array configured for use in a many-to-one configuration with the near-range resonant wireless power transmission system. [Figure 20B] Figure 19A shows a rear view of a solar cell array configured for use in a many-to-one configuration with the near-range resonant wireless power transmission system. [Figure 21A] Figure 19A shows a front view of a solar cell array configured for use in a one-to-one configuration with the near-range resonant wireless power transmission system. [Figure 21B] Figure 19A shows a rear view of a solar cell array configured for use in a one-to-one configuration with the near-range resonant wireless power transmission system. [Figure 22A]Figure 19A shows a front view of a solar cell array configured for use in a column-based configuration with the near-range resonant wireless power transmission system. [Figure 22B] Figure 19A shows a rear view of a solar cell array configured for use in a column-based configuration with the near-range resonant wireless power transmission system. [Figure 23] This diagram shows a flowchart illustrating a method for wirelessly transmitting power from a photovoltaic solar cell to a power load. [Figure 24] A flowchart illustrating another method for wirelessly transmitting power from a photovoltaic solar cell array to a power load is shown. [Figure 25] A flowchart illustrating another method for wirelessly transmitting power from a photovoltaic solar cell array to a power load is shown. [Figure 26] A flowchart illustrating another method for wirelessly transmitting power from a photovoltaic solar cell array to a power load is shown. [Figure 27A] A diagram shows a portion of an electric vehicle using one embodiment of a power transmission system. [Figure 27B] Another drawing shows a portion of an electric vehicle using one embodiment of a power transmission system. [Figure 28A] A diagram of a computer monitor using one embodiment of a power transmission system is shown. [Figure 28B] This shows a computer monitor using another embodiment of the power transmission system. [Figure 29] This flowchart shows how to transmit power from a DC power source to a power load. [Figure 30] A flowchart illustrating further methods for transmitting power from a DC power source to a power load is shown. [Figure 31] This flowchart shows a method for transmitting power between transmitting and receiving modules in a bimodal resonant short-range high-frequency power transmission system. [Figure 32] A schematic diagram of a bidirectional power transmission circuit device is shown. [Figure 33] This shows the implementation of a bidirectional power transmission circuit device. [Figure 34A]This shows the implementation of a bidirectional power transmission circuit device mounted on the same silicon wafer as the photocell. [Figure 34B] Figure 34A shows a combined device having a resonator on the surface of a silicon wafer. [Figure 35A] This document describes a short-range resonant wireless power transmission system for wirelessly transmitting power from a photovoltaic solar cell to an AC power load. [Figure 35B] This diagram illustrates a power transmission system for transmitting power from a photovoltaic solar cell to an AC power load. [Figure 36] A schematic diagram of a bidirectional power transmission circuit device is shown. [Figure 37A] A schematic diagram of a bidirectional power transmission system for transmitting power between a DC power source and an AC power load using the frequency difference between two high-frequency signals is shown. [Figure 37B] A schematic diagram of a bidirectional power transmission system for transmitting power between a DC power source and a variable power load, which may be AC ​​or DC, using the phase difference between two high-frequency signals is shown. [Figure 37C] A schematic diagram shows a bidirectional power transmission system for transmitting power between a DC power supply and a variable power load, which may be AC ​​or DC, using the phase difference of two high-frequency signals and multiple pairs of rectifiers / amplifiers. [Figure 37D] A schematic diagram of a bidirectional power transmission system for transmitting power between multiple DC power supplies and a variable power load, which may be AC ​​or DC, is shown, using the phase difference of two high-frequency signals and multiple pairs of HF switching signal generators and rectifiers / amplifiers. [Figure 38] The rectified power signal in half-wave train form and the result of unfolding the power signal are shown. [Figure 39] A flowchart shows a method for transmitting power between a DC power source and a variable power load, which may be AC ​​or DC. [Figure 40A] This shows a disassembled rear view of a solar cell module for wireless power transmission, which includes solar cells and a high-frequency power module. [Figure 40B]This shows a disassembled rear view of a solar module for wired power transmission, which includes solar cells and a high-frequency power module. [Figure 41A] This describes a power transmission system for wirelessly transmitting power from a solar cell to a variable power load that may be AC ​​or DC. [Figure 41B] This describes a power transmission system for wirelessly transmitting power from a solar cell to a variable power load that may be AC ​​or DC. [Figure 41C] This describes a power transmission system for wirelessly transmitting power from a solar cell to a variable power load that may be AC ​​or DC. [Figure 42A] This is a schematic exploded rear view of a solar panel for wireless power transmission based on an array of solar cell modules, before conformally applying the encapsulation layer. [Figure 42B] This is a schematic exploded rear view of a solar panel for wired power transmission based on an array of solar cell modules, before conformally applying the encapsulation layer. [Figure 43A] A schematic side view of a photovoltaic module sealed beneath a conformal sealing layer is shown. [Figure 43B] A schematic side view shows a further implementation of the photovoltaic module sealed beneath the conformal encapsulation layer. [Figure 44] This is a schematic exploded rear view of a solar panel for wireless power transmission based on an array of photovoltaic modules, including protective caps, before conformally applying the encapsulation layer. [Figure 45] This shows a flowchart of the process for manufacturing solar panels. [Modes for carrying out the invention]

[0131] Throughout the following description, certain details are provided to provide a complete understanding to those skilled in the art. However, to avoid unnecessarily obscuring the disclosure, well-known elements may not be illustrated or described in detail. Therefore, the descriptions and drawings should be considered illustrative rather than restrictive. One aspect of the present invention provides a wireless power transmission system comprising a transmitter (also referred to as the primary side) and a receiver (also referred to as the secondary side). Another aspect of the present invention provides a wireless power transmitter that can be used as part of another wireless power transmission system. Another aspect of the present invention provides a wireless power receiver that can be used as part of another wireless power transmission system. Transmitters according to some embodiments of the present invention may comprise a resonator configured to transmit power by inductive power transmission and / or capacitive power transmission. Similarly, receivers according to some embodiments of the present invention may comprise a resonator configured to receive power by inductive power transmission and / or capacitive power transmission.

[0132] Figure 1 is a simplified schematic diagram of a wireless power transmission (WPT) system 10 comprising a primary side 12 and a secondary side 14. The primary side 12 may also be referred to as the transmitter, and the secondary side 14 may also be referred to as the receiver. The primary side 12 comprises a transmitter module 20 and a transmitter resonator 30, and the secondary side 14 comprises a receiver module 40 and a receiver resonator 50.

[0133] The transmitter module 20 receives power as input, including, for example, direct current (DC) power. Although not shown, the transmitter module 20 may include, for example, an inverter, a transmitter compensation network, and / or other components as further described herein. The transmitter module 20 supplies power as output, including, for example, alternating current (AC) power, to the transmitter resonator 30.

[0134] The transmitter resonator 30 can receive power from the transmitter module 20 as input and output a magnetic field 31A (e.g., a time-varying magnetic field) and / or an electric field 31B (e.g., a time-varying electric field). In some embodiments, the transmitter resonator 30 outputs a magnetic field 31A for the IPT. In some embodiments, the transmitter resonator 30 outputs an electric field 31B for the CPT. In some embodiments, the resonator 30 outputs a magnetic field 31A and an electric field 31B simultaneously for the purpose of simultaneous power transmission through the CPT and IPT. In some embodiments, the resonator 30 can switch between outputting an electric field 31B for the CPT, outputting a magnetic field 31A for the IPT, and simultaneously outputting a magnetic field 31A and an electric field 31B for simultaneous power transmission through the CPT and IPT.

[0135] The adjective term "bimodal" is used herein to describe a system configured to perform capacitive and inductive signal transmission simultaneously.

[0136] In the presence of the magnetic field 31A, a current may be induced in the receiver resonator 50 due to the IPT. In the presence of the electric field 31B, an alternating potential may be induced in the receiver resonator 50 (or one or more of its antennas).

[0137] When a magnetic field 31A induces a current in the receiver resonator 50, such a current may be output to the receiver module 40. Similarly, when an electric field 31B induces an alternating potential in the receiver resonator 50, a current may flow from the receiver resonator 50 into the receiver module 40.

[0138] The receiver module 40 may receive power (e.g., AC power) from the receiver resonator 50 as input and output power (e.g., DC power) to a load. The load may be the charge of an energy storage device such as a battery or supercapacitor. In non-limiting examples, the load may include elements such as electric bicycles (also referred to as e-bikes or e-cycles), automobiles, and boats, such as e-cycles that are part of a bicycle-sharing fleet. Although not shown, the receiver module 40 may include, for example, a rectifier, a receiver compensation network, and / or other components that will be discussed further herein.

[0139] The WPT system 10 may be configured to adjust the ratio of the power transmitted from the transmitter module 20 to the receiver module 40 via the CPT to the power transmitted from the transmitter module 20 to the receiver module 40 via the IPT ("transmission mode ratio") for various reasons. For example, the transmission mode ratio may be adjusted to increase the proportion of power supplied by the CPT when the distance between the transmitter resonator 30 and the receiver resonator 50 increases; to increase the proportion of power supplied by the IPT when a living organism (e.g., a human or animal) is near the WPT system 10; to increase the proportion of power supplied by the CPT when an object (e.g., a metallic body) is near the WPT system 10; to increase the proportion of power supplied by the CPT when the alignment between the transmitter resonator 30 and the receiver resonator 50 deteriorates; and / or to perform any combination of the foregoing.

[0140] In some embodiments, the transmission mode ratio may be adjusted according to maximum power point tracking techniques, such as, but not limited to, “observe and perturb,” as sometimes used in wind turbines and solar panels (see, for example, “Adjustable Load With Tracking Loop to Improve RF Rectifier Efficiency Under Variable RF Input Power Conditions” by S. Dehghani, S. Abbasian, and T. Johnson, IEEE Transactions on Microwave Theory and Techniques, vol. 64, no. 2, pp. 343-352, Feb. 2016). In some embodiments, the transmission mode ratio may be adjusted according to machine learning algorithms. For example, in some embodiments, if the WPT system 10 determines that the WPT efficiency is undesirably low, the WPT system 10 may increase the proportion of power supplied by the CPT (or IPT). If increasing the reliance on the CPT (or IPT) negatively impacts the WPT efficiency, the WPT system 10 may decrease its reliance on the CPT (or IPT). This process may be repeated until the desired / maximum WPT efficiency is achieved.

[0141] Each of the transmitter resonator 30 and the receiver resonator 50 may include multiple antennas 80 arranged in various configurations.

[0142] Antenna 80 may be any suitable antenna having high self-inductance and high self-capacitance that can generate both a magnetic field 31A and an electric field 31B for CPT and IPT (separately and / or simultaneously). Figures 2A, 2B and 2C show non-limiting examples of antennas 80, 180, and 280. For the purposes of this specification, “high self-inductance” is a self-inductance large enough to allow the antenna to generate a magnetic field suitable for the purposes of IPT. Similarly, for the purposes of this specification, “high self-capacitance” is a self-capacitance large enough to allow the antenna to generate an electric field suitable for the purposes of CPT.

[0143] Figure 2A shows an antenna 80 according to one embodiment of the present invention. The antenna 80 may include any suitable conductive material. For example, the antenna 80 may include copper, gold, silver, aluminum, other suitable materials, or a combination thereof. As can be seen from Figure 2A, the antenna 80 comprises an elongated element 80A having a rectangular (e.g., square) cross-section, which is bent or formed into a substantially planar rectangular (in the XY plane) coil shape such that adjacent wrappings of the elongated element 80A are separated by a gap 80B. The gap 80B is shown to be substantially constant along the length of the elongated element 80, but this is not required.

[0144] To increase the self-inductance of antenna 80, the size of the gap 80B may be reduced. To increase the self-capacitance of antenna 80, the number of bends (e.g., bend 82A) of the elongated element 80A may be increased, the number of corners and edges (e.g., edge 82B) of the elongated element 80A may be increased, the length of the elongated element 80A may be increased, and / or the thickness 80C of the elongated element 80A may be increased.

[0145] Figure 2B shows another non-limiting example of antenna 180 according to another embodiment of the present invention. Antenna 180 is substantially similar to the first antenna 80, except that, instead of being bent or formed into a substantially planar rectangular coil shape as shown in Figure 2B, the elongated elements 180A are bent or formed into a substantially planar zigzag shape with right-angle corners. Similar to antenna 80, adjacent zigzags or zags of the elongated elements 180A are spaced apart by gaps 180B. The gaps 180B are shown to be substantially constant along the length of the elongated elements 180, but this is not mandatory.

[0146] To increase the self-inductance of antenna 180, the size of gap 180B may be reduced. To increase the self-capacitance of antenna 180, the number of bends (e.g., bend 182A) of the elongated element 180A may be increased, the number of corners and edges (e.g., edge 182B) of the elongated element 180A may be increased, and / or the thickness 180C of the elongated element 180A may be increased.

[0147] Figure 2C shows another non-limiting example of an antenna 280 according to another embodiment of the present invention. Antenna 280 is substantially similar to the first antenna 80, except that instead of being bent or formed into the shape of a substantially planar rectangular coil, an elongated element 280A is bent or formed as a hub element 280A in a substantially planar circular shape (in the XY plane), and sector elements 280C extend radially outward from the hub element 280A. Adjacent sector elements 280C are separated from each other by a gap 280B.

[0148] To increase the self-inductance of antenna 280, the size of gap 280B may be reduced. To increase the self-capacitance of antenna 280, the number of sectors 280C may be increased, the number of corners and edges (e.g., edge 282A) of hub 280A and / or sector 280C may be increased, and / or the thickness 280C of elongated hub 280A and / or sector 280C may be increased.

[0149] Figures 2A, 2B, and 2C show exemplary, non-limiting embodiments of antennas 80, 180, and 280, but it should be understood that many other shapes and configurations of suitable antenna 80 may be used in the resonators described herein. Non-limiting examples of modifications that can be made to the illustrated antennas include changing the cross-sectional shape of the elongated elements 80A, 180A to something other than rectangular (e.g., triangular, circular, hexagonal, etc.), changing the 90° bends 82A, 182A to non-90° or to make them round, changing the XY planar shape of the first transmitter antenna 80 to something other than rectangular or circular, and using non-repeating patterns such as bends and corners.

[0150] Antennas 80, 180, and 280 are described and illustrated herein as being relatively flat or planar (e.g., with substantially no change in thickness in the Z direction), but this is not essential. In some embodiments, antennas 80, 180, and 280 may have a conical concave or conical cone shape, as shown in Figures 3A and 3B. For example, the antennas herein may have a conical helix shape (not shown). In some embodiments, antenna 80 may have a rectangular conical helix shape such that the inner winding of antenna 80 is spaced apart in the Z direction from the outer winding of antenna 80. Such a conical shape may allow the resonator to be used for a wider range of resonant frequencies. In other embodiments, the thickness of the first transmitter antenna in the Z direction may vary in other ways.

[0151] Antennas 80, 180, and 280 may be arranged in a configuration similar to that of a plate in a CPT WPT system, for example. For example, in a two-antenna WPT system according to one embodiment of the present invention, the transmitter resonator 30 may include a first transmitter antenna 32 arranged parallel to the first receiver antenna 52 of the receiver resonator 50, as shown in Figure 4A. For CPT, the mutual capacitance between the two antennas 32, 52 provides a path for current to flow forward to the receiver side, and a conductive path (e.g., ground) allows current to flow backward to the transmitter side. For IPT, driving current through the first transmitter antenna 32 generates a magnetic field 31A that can induce current in the first receiver antenna 52. For CPT, a voltage may be applied to the first transmitter antenna 32 to create a potential difference between the first transmitter antenna 32 and the first receiver antenna 52, thereby generating an electric field 31B.

[0152] The first transmitter antenna 32 may comprise any suitable antenna having high self-inductance and high self-capacitance that can generate both a magnetic field 31A and an electric field 31B (separately and / or simultaneously). For example, the first transmitter antenna may comprise one of antennas 80, 180, 280, or any other antenna described herein.

[0153] The first receiver antenna 52 may comprise any suitable antenna having high self-inductance and high self-capacitance, which may have a current induced therein by a magnetic field 31A and a potential difference therein by an electric field 31B (separately and / or simultaneously). In some embodiments, the first receiver antenna 52 may be substantially the same as the first transmitter antenna 32 (for example, the first receiver antenna 52 may have the same characteristics as any of the antennas described or illustrated herein). In some embodiments, the antennas 32, 52 may be different from each other (for example, the first transmitter antenna 32 may comprise antenna 80 and the first receiver antenna 52 may comprise antenna 180).

[0154] In some embodiments, in order to improve the coupling between the first transmitter antenna 32 and the first receiver antenna 52, the XY plane region of the first transmitter antenna 32 is smaller than the XY plane region of the first receiver antenna 52.

[0155] Figure 4B shows another example of the antenna configurations 80, 180, and 280. In particular, Figure 4B shows a 4-antenna stack (or 4-antenna vertical) WPT system. Each of the transmitter resonator 130 and receiver resonator 150 has two antennas. One antenna of the transmitter resonator 30 and one antenna of the receiver resonator 150 both provide a forward path for power, and the other antenna of the transmitter resonator 130 and the other antenna of the receiver resonator 150 both provide a return path for power.

[0156] For IPT, a magnetic field capable of inducing current in the first receiver antenna 152 and the second receiver antenna 154 is generated by driving current through the transmitter antennas 132 and 134. For CPT, an electric field (31B shown in Figure 1) may be generated by applying a potential difference between the first antenna 132 and the second antenna 134, thereby inducing a potential across the first receiver antenna 152 and the second receiver antenna 154.

[0157] As shown in Figure 4B, the transmitter resonator 130 comprises a first transmitter antenna 132 and a second transmitter antenna 134 separated in the Z direction by a spacer 138.

[0158] The first transmitter antenna 132 may comprise any suitable antenna having high self-inductance and high self-capacitance that can generate both a magnetic field 31A and an electric field 31B (separately and / or simultaneously). For example, the first transmitter antenna may comprise one of antennas 80, 180, 280, or any other antenna described herein.

[0159] The spacer 138 may contain any suitable material. For example, the spacer 138 may contain air, a dielectric material, ferrite, or any combination thereof. The spacer 138 may have a dielectric constant selected to vary the electric field 31A and / or a permeability constant selected to vary the magnetic field 31B. The spacer 138 may contain a high dielectric constant material to increase the capacitance of the transmitter resonator 130. The thickness and planar area of ​​the spacer 138 may depend on the thickness and / or planar area of ​​the first transmitter antenna 132 and the second transmitter antenna 134. In some embodiments, electrical isolation is desirable, and a low dielectric constant material may be used for the spacer 138 (e.g., for shielding).

[0160] The second transmitter antenna 134 may comprise any suitable antenna having high self-inductance and high self-capacitance that can generate both a magnetic field 31A and an electric field 31B (separately and / or simultaneously). In some embodiments, the second transmitter antenna 134 may be substantially similar to the first transmitter antenna 132 (for example, the second transmitter antenna 134 may have the same characteristics as any of the antennas described or illustrated herein). In some embodiments, the first transmitter antennas 132 and the second transmitter antenna 134 and the first receiver antennas 152 and the second receiver antenna 154 may be different from each other (for example, the first transmitter antennas 132 and the second transmitter antenna 134 may be similar to antenna 80, and the first receiver antennas 152 and the second receiver antenna 154 may be similar to antenna 180).

[0161] In some embodiments, the XY plane region of the second transmitter antenna 134 may be a different size from the XY plane region of the first transmitter antenna 132. In some embodiments, the XY plane region of the second transmitter antenna 134 may be smaller than that of the first transmitter antenna 132 to ensure coupling between each pair of antennas. In some embodiments, the XY plane region of the second transmitter antenna 134 may be larger than that of the first transmitter antenna 132.

[0162] In some embodiments, the second transmitter antenna 134 is substantially complementary to the first transmitter antenna 132 in size and / or shape such that the first transmitter antenna 132 does not substantially overlap with the second transmitter antenna 134 in the Z direction. Figure 5 shows a schematic XZ planar section of a portion of the transmitter resonator 130, where the first transmitter antenna 132 and the second transmitter antenna 134 are substantially the same shape as the first transmitter antenna 180 in Figure 2B. As can be seen from the figure, the elongated elements 132A of the first transmitter antenna 132, specifically portions 132A-1, 132A-2, and 132A-3, overlap in the Z direction with the gaps 134B-1, 134B-2, and 134B-3 of the second transmitter antenna 134 (for example, a line directed in the Z direction passing through portion 132A-1 of the elongated element 132A of the first antenna 132 also passes through the gap 134B-1 of the second antenna 134). (For example, a line oriented in the Z direction passing through part 134A-1 of the elongated element 134A of the second transmitter antenna 134 passes through gap 132B-1, 132B-2, 132B-3 of the first transmitter antenna 132 in the Z direction (for example, a line oriented in the Z direction passing through part 134A-1 of the elongated element 134A of the second antenna 134 passes through gap 132B-1 of the second antenna 134). The complementary shapes of the first transmitter antenna 132 and the second antenna 134 can reduce parasitic energy losses experienced by the transmitter resonator 130. In some embodiments, the first transmitter antenna 132 and the second transmitter antenna 134 do not have to be perfectly complementary, but may have one or more complementary parts.

[0163] The receiver resonator 150 comprises a first receiver antenna 152 and a second receiver antenna 154 separated in the Z direction by a spacer 158. The first receiver antenna 152 may be substantially similar to any of antennas 80, 180, or 280, or other as described herein. The second receiver antenna 154 may also be substantially similar to any of antennas 80, 180, or 280, or other as described herein. Similar to the first transmitter antenna 132 and the second transmitter antenna 134, the first receiver antenna 152 and the second receiver antenna 154 may be complementary (or partially complementary) in size and / or shape.

[0164] In some embodiments, to adjust the self-inductance or self-capacitance of the receiver resonator 150, the XY plane regions of the first receiver antenna 152 and the second receiver antenna 154 are different from those of the first transmitter antenna and the second transmitter antenna, as shown in Figure 4B. For example, in some embodiments, as shown in Figure 2A, the XY plane regions of the first receiver antenna 152 and the second receiver antenna 154 are larger than those of the first transmitter antenna 132 and the second transmitter antenna 134. Such a difference in XY plane regions can improve the receiver resonator 150's ability to capture more magnetic fields 31A and / or electric fields 31B.

[0165] Spacer 158 may be equipped with any suitable spacer. Spacer 158 may contain the same or similar material as spacer 138, or a different material than spacer 138. Compared to spacer 158, spacer 138 may have a smaller dimension in the Z direction to achieve the desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14, and the impedance of the primary side 12. Different compensation networks may be used on both the primary side 12 and the secondary side 14 to accommodate such changes in coupling coefficient and impedance.

[0166] Compared to the four-antenna parallel structure shown in Figure 4C, the stacked configuration in Figure 4B is much more compact in the XY plane. Furthermore, this configuration is robust to angular misalignment because all antennas can be centered. Specifically, if the antennas are circular, angular rotation does not affect the coupling capacitance. However, compared to the four-antenna parallel structure shown in Figure 4C, the transconductance of the stacked configuration in Figure 4B may be lower due to the increased cross-coupling capacitance.

[0167] Figure 4C shows another example of the antenna configurations 80, 180, and 280. In particular, Figure 4C shows a four-antenna parallel (or four-antenna horizontal) WPT system. Each of the transmitter resonator 230 and receiver resonator 250 has two antennas. One antenna of the transmitter resonator 230 and one antenna of the receiver resonator 250 both provide a forward path for power, and the other antenna of the transmitter resonator 230 and the other antenna of the receiver resonator 250 both provide a return path for power.

[0168] For IPT, a magnetic field capable of inducing current in the first receiver antenna 252 and the second receiver antenna 254 is generated by driving current through the transmitter antennas 232 and 234. For CPT, an electric field 31B may be generated by applying a potential difference between the first antenna 232 and the second antenna 234, thereby inducing a potential across the first receiver antenna 252 and the second receiver antenna 254.

[0169] Compared to the transmitter resonator 130 and receiver resonator 150 shown in Figure 4B, the transmitter resonator 230 and receiver resonator 250, which have a horizontal antenna configuration, may be desirable in applications where there are limitations on the Z-axis dimension of the resonator.

[0170] The transmitter resonator 230 comprises a first transmitter antenna 232 and a second transmitter antenna 234 separated in the X direction by a spacer 238. Separating the first transmitter antenna 232 and the second transmitter antenna 234 in the X direction can reduce parasitic energy losses. The first transmitter antenna 232 and the second transmitter antenna 234 may be substantially the same as the first transmitter antenna 132 and the second transmitter antenna 134, and the spacer 238 may be substantially the same as the spacer 138. Similar to the transmitter resonator 130, the first transmitter antenna 232 may have a larger XY plane region than the second transmitter antenna 234 to improve the forward path for power transmission.

[0171] The spacer 238 may contain any suitable material. For example, the spacer 238 may contain air, a dielectric material, ferrite, or a combination thereof. The spacer 238 may have a dielectric constant selected to vary the electric field 31A and / or a permeability constant selected to vary the magnetic field 31B. The spacer 238 may contain a high dielectric constant material to increase the capacitance of the transmitter resonator 230. The thickness and planar area of ​​the spacer 238 may depend on the thickness and / or planar area of ​​the first transmitter antenna 232 and the second transmitter antenna 234. In some embodiments, electrical isolation is desirable, and a low dielectric constant material may be used for the spacer 238 (e.g., for shielding).

[0172] The receiver resonator 250 comprises a first receiver antenna 252 and a second receiver antenna 254 separated in the X direction by a spacer 258. Separating the first receiver antenna 252 and the second receiver antenna 254 in the X direction can reduce parasitic energy loss. The first receiver antenna 252 and the second receiver antenna 254 may be substantially the same as the first receiver antenna 152 and the second receiver antenna 154, and the spacer 258 may be substantially the same as the spacer 138. Similar to the receiver resonator 150, the first receiver antenna 252 may have a larger XY plane region than the second receiver antenna 254.

[0173] Spacer 258 may be equipped with any suitable spacer. Spacer 258 may contain the same or similar material as spacer 238, or a different material than spacer 238. Compared to spacer 258, spacer 238 may have a smaller Z-direction dimension to achieve the desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14, and the impedance of the primary side 12. Different compensation networks may be used on both the primary side 12 and the secondary side 14 to accommodate such changes in coupling coefficient and impedance.

[0174] In some embodiments, the XY plane region of spacer 258 may differ from that of spacer 238 in order to change the self-inductance or self-capacitance of the transmitter resonator 230 or receiver resonator 250. For example, compared to spacer 258, spacer 238 may have a smaller XY plane region, as shown in the figure.

[0175] Figure 4D shows another example of the antenna configurations 80, 180, and 280. In particular, Figure 4D shows a 6-antenna WPT system combining the stack configuration of Figure 4B and the parallel configuration of Figure 4C. Each of the transmitter resonator 130 and receiver resonator 150 has three antennas. One antenna of the first transmitter antenna 332 and the second transmitter antenna 334 and one of the first receiver antenna 352 and the second receiver antenna 354 together provide a forward path for power, and the other antenna of the first transmitter antenna 332 and the second transmitter antenna 334 and the other antenna of the first antenna 352 and the second antenna 354 together provide a return path for power. The third transmitter antenna 336 and the third receiver antenna 356 act as auxiliary antennas, increasing the equivalent self-capacitance and functioning as field shielding. In some embodiments, the third transmitter antenna 336 and the third receiver antenna 356 are passive (for example, no potential difference is applied between the third transmitter antenna 336 and the third receiver antenna 356, and / or no current is driven through the third transmitter antenna 336 and the third receiver antenna 356). For IPT, a magnetic field is generated that can induce a current in the first receiver antennas 352, 354, and 356 by driving a current through one or more of the transmitter antennas 332, 334, and 336. For CPT, a voltage may be applied to the first transmitter antenna 332, the second transmitter antenna 334, and / or the third transmitter antenna 336 to create a potential difference between any of the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336, thereby generating an electric field 31B.

[0176] The transmitter resonator 330 comprises a first transmitter antenna 332 and a second transmitter antenna 334 separated in the X direction by a spacer 338, and a third transmitter antenna 336 separated from the first and second transmitter antennas and spacer 338 by a second spacer 339. The third transmitter antenna 336 may provide electric field shielding to reduce undesirable leakage of electric fields from the transmitter resonator 330. The third transmitter antenna 336 may include a ferrite sheet or ferrite surface to provide magnetic field shielding to reduce undesirable leakage of magnetic fields from the transmitter resonator 330. By modifying the spacer 339, shielding or shaping of electric or magnetic fields may also be possible.

[0177] The first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336 may be substantially the same as either the first transmitter antenna 132 or the second transmitter antenna 134. Spacers 338 and 339 may be substantially the same as spacer 138. Similar to the transmitter resonator 130, the first transmitter antenna 332 may have a larger XY plane region than the second transmitter antenna 334. The third transmitter antenna 336 may have a larger XY plane region than either the first transmitter antenna or the second transmitter antennas 334 or 332.

[0178] Spacers 338, 339 may contain any suitable material. For example, spacers 338, 339 may contain air, a dielectric material, ferrite, or a combination thereof. Spacers 338, 339 may have a dielectric constant selected to vary the electric field 31A and / or a permeability constant selected to vary the magnetic field 31B. Spacers 338, 339 may contain a high dielectric constant material to increase the capacitance of the transmitter resonator 230. The thickness and planar area of ​​spacers 338, 339 may depend on the thickness and / or planar area of ​​the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336. In some embodiments, electrical isolation is desirable, and low dielectric constant materials may be used for spacers 338, 339 (e.g., for shielding).

[0179] The receiver resonator 350 comprises a first receiver antenna 352 and a second receiver antenna 354 separated in the X direction by a spacer 358, and a third receiver antenna 356 separated from the first and second receiver antennas and spacer 358 by a second spacer 359. The third receiver antenna 356 may provide electric field shielding to reduce undesirable electric field leakage from the receiver resonator 350. The third receiver antenna 356 may include a ferrite sheet or ferrite surface to provide magnetic field shielding to reduce undesirable magnetic field leakage from the transmitter. By modifying spacer 359, shielding or shaping of electric or magnetic fields may also be possible. The first receiver antenna 352 and the second receiver antenna 354 and the third receiver antenna 356 may be substantially the same as either the first receiver antenna 152 or the second receiver antenna 154. Spacers 358 and 359 may be substantially the same as spacer 158. Similar to the receiver resonator 150, the first receiver antenna 352 may have a larger XY plane region than the second receiver antenna 354. The third receiver antenna 356 may have a larger XY plane region than either the first receiver antenna 354 or the second receiver antenna 352.

[0180] Spacers 358 and 359 may be fitted with any suitable spacers. Spacers 358 and 359 may contain the same or similar material as spacers 338 and 339, or a different material than spacers 338 and 339. Compared to spacers 358 and 359, spacers 338 and 339 may have smaller dimensions in the Z direction to achieve the desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14, and the impedance of the primary side 12. Different compensation networks may be used on both the primary side 12 and the secondary side 14 to accommodate such changes in coupling coefficient and impedance.

[0181] In some embodiments, the XY plane region of spacer 358 may differ from the XY plane region of spacer 338 in order to change the self-inductance or self-capacitance of the transmitter resonator 330 or receiver resonator 350. For example, spacer 338 may have a smaller dimension in the X direction compared to spacer 358. In some embodiments, the Z direction dimension of spacer 359 may differ from the Z direction dimension of spacer 339 in order to change the self-inductance or self-capacitance of the transmitter resonator 330 or receiver resonator 350. For example, spacer 339 may have a smaller dimension in the Z direction compared to spacer 359. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14, and the impedance of the primary side 12. Different compensation networks may be used on both the primary side 12 and the secondary side 14 to accommodate such changes in coupling coefficient and impedance.

[0182] In some embodiments, magnetic shielding may be provided around one or more of the transmitter resonators 30 and receiver resonators 50. For example, ferrite may be used as magnetic shielding to reduce undesirable eddy currents in nearby metal bodies. Ferrite (or another suitable material) may also be used to isolate the transmitter resonator 30 and / or receiver resonator 50 from surrounding metal bodies, and thus may function to increase the antenna's self-inductance and / or the resonator's mutual inductance.

[0183] Figure 6 shows a schematic diagram of the primary side 12 comprising a transmitter module 20 and a transmitter resonator 30 according to one embodiment of the present invention. The transmitter resonator 30 may comprise any of the transmitter resonators 30, 130, 230, 330, or other described herein.

[0184] The transmitter module 20 includes a controller 22. The controller 22 receives various inputs from sensors 24 (e.g., load detector 24A, transmitter power sensor 24B, surrounding object detector 24C and / or distance detector 24D) and outputs control signals to various components 26 (e.g., oscillator 26A, power amplifier 26B, filter network 26C, matching network 26D, compensation network 26E and V / I tuner 26F).

[0185] The load detector 24A is configured to detect the presence of a load 70 (shown in Figure 7) connected to the secondary side 14. The load 70 may be, for example, a battery of an electric vehicle such as an e-cycle or electric car, or any other suitable item requiring a power input. The load detector 24A may be implemented with a physical sensor (e.g., an optical sensor, pressure sensor, infrared sensor, or proximity sensor, but not limited to) and appropriate software or firmware. For example, in some embodiments, power (e.g., current and voltage) is measured, for example, at point 24E, to determine the power consumed by the transmitter resonator 30 (e.g., measured by the transmitter power sensor 24B). If the amount of power drawn by the transmitter resonator 30 increases above a baseline, the load detector 24A may signal to the controller 22 that a load 70 is present.

[0186] In other embodiments, the load detector 24A may be configured to measure the input impedance of the transmitter resonator 30 that the transmitter module 20 receives at point 24E. For example, the presence of a resonant load adjacent to the transmitter resonator 30, including a secondary side 14 configured to drive a load 70, changes the input impedance of the transmitter resonator 30. This change in impedance, as provided to the controller 22 by the load detector 24A, can be used by the transmitter controller 22 to determine whether a cooperating receiver is present adjacent to the transmitter resonator 30. Because the impedance changes induced in the transmitter resonator 30 by different receivers are very distinct and characteristic, the controller 22 can not only detect the presence or absence of a receiver adjacent to the transmitter resonator 30 but also identify its type, for example, various models of mobile phones and digital tablets, but not limited to these.

[0187] The transmitter power sensor 24B may measure power at point 24E (for example, current and voltage) to determine how much power is being drawn by the transmitter resonator 30. Such information may be used, for example, by the load detector 24A, or to determine whether there is a desirable and efficient coupling between the transmitter resonator 30 and the receiver resonator 50.

[0188] The ambient object detector (SOD) 24C is configured to determine whether an object (e.g., a living thing such as a human or animal, or an inanimate object such as a piece of metal, or something else) is in proximity to the transmitter resonator 30. The SOD 24C may be implemented by a physical sensor (e.g., an optical sensor, pressure sensor, infrared sensor, proximity sensor, RADAR, or LIDAR, but not limited to these) or by appropriate software or firmware. For example, if the power consumed by the transmitter resonator 30 (measured by the transmitter power sensor 24B) decreases during IPT, the SOD software may determine that a piece of metal (or any conductor) is in proximity to the transmitter resonator 30 or the receiver resonator 50, and the SOD may provide a signal to the controller 22 indicating such presence. In some embodiments, the controller 22 may increase the proportion of power supplied by the CPT to the transmitter module 20 when a metal object is detected to be in proximity to the transmitter resonator 30 or the receiver resonator 50. The controller 22 may be configured to increase the power supply to the transmitter resonator 30 (for example, to a level higher than the regulatory level when organisms are present) when SOD24C detects that organisms are in close proximity, or to reduce the power supply to the transmitter resonator 30 to below the regulatory level when SOD24C detects that organisms are in close proximity.

[0189] The distance detector 24D is configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50. The distance detector 24D may be implemented by a physical sensor (e.g., an optical sensor, ultrasonic sensor, infrared sensor, proximity sensor, RADAR, or LIDAR, but not limited to these) or by appropriate software or firmware. For example, the distance detector 24D may be configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50 based on changes in the transmitted power measured by the transmitter power sensor 24B.

[0190] In one embodiment, one or more temperature sensors may monitor the temperature of the transmitter resonator 30 or the receiver resonator 50. If the temperature exceeds a predetermined limit, the controller 22 may reduce the proportion of power supplied to the transmitter module 20 by the IPT, reduce the overall power supply to the transmitter resonator 30, or cut off the power supply to the transmitter resonator 30 to prevent fire hazards or thermal runaway.

[0191] The oscillator 26A may be configured to control the frequency band and / or bandwidth and / or duty cycle (phase) (e.g., 5% to 50%) of the current supplied to the transmitter resonator 30 in response to the signal from the controller 22.

[0192] The power amplifier 26B can be used to convert DC power to AC power. The power amplifier 26B can be used to adjust the power supplied to the transmitter resonator 30 in response to signals from the controller 22. In particular, the controller 22 can send signals to the power amplifier 26B to adjust its reflection coefficient. In some embodiments, the controller 22 may send signals to the power amplifier 26B to turn it off (or sleep) when the load detector 24A does not detect a load, or to turn it on when the load detector 24A detects a load.

[0193] The power amplifier 26B may comprise a switch-mode power amplifier (single-ended mode or differential configuration) that can be configured to receive a square (sine) wave from the oscillator 26A and generate a sine wave of a specific frequency desired to drive the transmitter resonator 30. Figure 8 is a schematic diagram of an exemplary power amplifier 26B that can be used in the transmitter 30. The power amplifier 26B may also comprise a differential switch-mode amplifier. The power amplifier 26B has three inputs: two input signals that drive active devices (transistors) 127C and 127D at frequencies set to resonant frequencies, and a DC voltage of a power supply 127E used to control the output power and operating area of ​​the active devices.

[0194] Various load terminations are used to improve performance (e.g., output power, power conversion efficiency) and reduce unwanted harmonic levels. In particular, a third harmonic termination 127F is located in a series branch to shape the voltage waveform at the drain node 127G. A second harmonic termination 127H is located in a parallel branch to shape the voltage waveform at the drain node 127G. A first harmonic termination 127I is located in a series branch to shape the voltage waveform at the drain node 127G. The effect of the third harmonic termination may be considered in the second harmonic termination and the first harmonic terminations 127H, 127I. The effect of the second harmonic termination may be considered in the first harmonic termination 127I. In the differential configuration of the power amplifier 26B, an AC load 127J (receiving output power) is placed in series. The charge AC load 127J may be a function of the transmitter resonator 30, the receiver resonator 50, and / or their alignment and position. The power amplifier 26B may be configured to generate sufficient power to the transmitter resonator 30 so that an electric field, or a magnetic field, or any combination of an electric field and a magnetic field, is generated by the transmitter resonator 30 and captured by the receiver resonator 50.

[0195] The amplifier 26B may have two phase shifters 127L in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifters 127L adjust the appropriate phase difference between the AC signal overload 127J and the gate signals of transistors 127C and 127D. The phase difference between the gate signals and the AC signal overload 127J can change the performance of the power amplifier, such as the power conversion efficiency and the operating range of the transistors. It can also change the output impedance of transistors 127C and 127D and / or the optimal AC load 127J of the power amplifier 26B.

[0196] Amplifier 26B may have two level shifters 127K in a differential configuration (but only one level shifter in a single-ended configuration). The level shifters 127K can adjust the appropriate amplitude of the gate signals of transistors 127C and 127D. The amplitude level of the gate signals can change the performance of the amplifier (e.g., power conversion efficiency and the operating range of the transistors).

[0197] Amplifier 26B may be reconfigurable to function as a rectifier, particularly a self-synchronous rectifier. As part of such reconfiguration, the integrated phase shifter 127L and integrated level shifter 127K may be adjusted to allow amplifier 26B to function as rectifier 26B based on the inherent amplification and switching capabilities of transistors 127C and 127D. This reconfigurability of amplifier 26B between amplifier and rectifier operation allows the transmitter module 20 to be controllably reconfigured between transmitter mode and receiver mode, respectively. Reconfiguration can be performed under command from controller 22. When amplifier 26B is reconfigured from amplifier to rectifier, the AC load 127J changes to AC source 127J. Correspondingly, when amplifier 26B is reconfigured from amplifier to rectifier, the DC source 127E is reconfigured to a DC load. The application of transmitter module 20 in receiver mode will be discussed below, after the secondary side 14 and its receiver module (both shown in detail in Figure 7) have been described.

[0198] The filter network 26C can adjust the frequency response, such as bandwidth, cutoff frequency, 3dB frequency, and gain, provided to the transmitter resonator 30 in response to the signal from the controller 22. The filter network may also be configured to adjust the waveform shape of the power from the transmitter module 20 to improve the efficiency of the transmitter module 20.

[0199] The matching network 26D may be configured to adjust the impedance to match the output of the power amplifier 26B to the transmitter resonator 30.

[0200] The compensation network 26E is provided to drive the transmitter resonator 30 at a desired resonant frequency (e.g., the resonant frequency of the receiver resonator), thereby increasing mutual flux, reducing heat generation, and improving power transmission efficiency. The compensation network 26E may comprise one or more capacitors for increasing capacitance and one or more inductors for increasing inductance. The compensation network 26E may be configured to increase capacitance (and / or decrease inductance) and increase inductance (and / or decrease capacitance) as needed. If the transmission mode ratio is 100% for a CPT, the compensation network 26E may function similarly to any known CPT compensation network (e.g., the compensation network 26E may function to increase inductance). Similarly, if the transmission mode ratio is 100% for an IPT, the compensation network 26E may function similarly to any known IPT compensation network (e.g., the compensation network 26E may function to increase capacitance). However, when the transmission mode is partially CPT and partially IPT, less compensation is required because the capacitance of the transmitter resonator 30 naturally compensates for the inductance of the transmitter resonator 30, and the inductance of the transmitter resonator 30 naturally compensates for the capacitance of the transmitter resonator 30. For example, with approximately 50% IPT and 50% CPT (e.g., a transmission mode ratio equal to 1), a compensation network may not be necessary at all, or its use may be substantially limited, thereby improving the efficiency of the WPT system 10.

[0201] As another example, between approximately 40-60% IPT and 40-60% CPT, a compensation network may not be necessary at all, or its use may be substantially limited, thereby improving the efficiency of the WPT system 10. For this reason, the compensation network 26E may have fewer or smaller inductors and / or capacitors compared to CPT WPT systems and / or pure IPT WPT systems that require considerable compensation. In some embodiments, if the capacitance of the transmitter resonator 30 is sufficiently low, the compensation network 26E may provide additional compensation. Similarly, if the inductance of the transmitter resonator 30 is sufficiently low, the compensation network 26E may provide additional compensation. The controller 22 may signal to the compensation network 26E how much and what type of compensation is needed, based, for example, the transmission mode ratio, the distance between the transmitter resonator 30 and the receiver resonator 50, the amount of power consumed by the transmitter resonator 30, and the power transmission efficiency.

[0202] In some embodiments, the magnitude of compensation by the compensation network 26E (e.g., an increase in capacitance or an increase in inductance) is proportional to the absolute difference between the transmission mode ratio and 1. For example, when the transmission mode ratio is greater than 1, the compensation network 26E functions to increase inductance, and as the transmission mode ratio increases beyond 1, the amount of inductance increase may increase. Similarly, when the transmission mode ratio is less than 1, the compensation network 26E functions to increase capacitance, and as the transmission mode ratio decreases by less than 1, the amount of capacitance increase may increase.

[0203] In some embodiments, the compensation network 26E may be configured to modulate the signal provided to the transmitter resonator 30 with information, thereby functioning as a source transmit modulator. The information for modulating the signal provided to the transmitter resonator 30 may be provided to the compensation network 26E by the controller 22. The information may include control data destined for the controller 42 of the receiver module 40 via the receiver resonator 50. The controller 42 is described in more detail below with reference to Figure 7. In other embodiments, the power amplifier 26B may function as a source transmit modulator. In yet another embodiment, the oscillator 26A may function as a source transmit modulator. The modulation used by the selected source transmit modulator may be amplitude modulation, frequency modulation, or phase modulation. The information may be modulated on the signal provided to the transmitter resonator 30 in digital or analog form. The information may be modulated to the resonant frequency of the power signal provided to the transmitter resonator 30 by the source transmit modulator. In other embodiments, the information may be modulated to a frequency different from the power transmission frequency. In other embodiments, the information may be modulated to harmonics of the resonant frequency of the power signal supplied to the transmitter resonator 30. In yet another embodiment, the resonant frequency of the power signal supplied to the transmitter resonator 30 may be a harmonic of the frequency of the signal on which the information is modulated. The V / I tuner 26F, described in more detail below, may transmit an information signal to the transmitter resonator 30 and thereby be configured to be transparent with respect to the transmitted information. The information transmitted in the manner described herein may include, but is not limited to, the operating mode of the module 20, the number and type of the receiver 40, ambient object sensor information, and load condition monitoring information, such as battery charge status, load voltage, and load current.

[0204] An embodiment of the V / I tuner 26F is shown in detail in Figure 10. The input signal to the V / I tuner 26F, received from the matched network 26E (Figure 6), is split by the splitter 262, having two mutually asymmetric paths 261A and 261B for the input signal. The first phase shifter 264A and the second phase shifter 264B generate a phase difference between the input voltage and input current of the transmitter resonator 30 (Figure 6). The first phase shifter 264A is controlled by the controller 22 (Figure 6) via the first phase-shift splitter control line 263A, and the second phase shifter 264B is controlled by the controller 22 (see Figure 6) via the second phase-shift splitter control line 263B. The first active switch 266A and the second active switch 266B receive signals from the first phase shifter 264A and the second phase shifter 264B, respectively, and are controlled by the controller 22 via the first active switch control line 265A and the second active switch control line 265B, respectively. The first active switch 266A and the second active switch 266B function to adjust the imaginary part of the signals received from the first phase shifter 264A and the second phase shifter 264B, respectively. Passive signal shaping networks 268A and 268B receive the adjusted signals from the first active switch 266A and the second active switch 266B, respectively. The passive signal shaping networks 268A and 268B function to fine-tune the signals received from the first active switch 266A and the second active switch 266B, respectively, and in particular to reduce the harmonics of these signals before passing them to the coupler 269. The signals provided along the two mutually asymmetric paths 261A and 261B are coupled by the coupler 269 and provided to the transmitter resonator 30. In other embodiments, the first phase shifter 264A and the second phase shifter 264B may be coupled as a single phase shifter receiving the input signal to the V / I tuner 26F, and the coupled phase shifter may have two separate outputs as active switches 266A and 266B.

[0205] The V / I tuner 26F adjusts the transmission mode ratio by adjusting the phase difference between the input current and input voltage to the transmitter resonator 30 in response to a signal from the controller 22. The real part of the impedance as seen from the transmitter module 20 is adjusted by phase shifters 264A and 264B, and its imaginary part can be adjusted by switches 266A and 266B. For example, a 90-degree phase shift every 3 milliseconds for every 10 milliseconds can result in 30% magnetic transmission and 70% power transmission.

[0206] The V / I tuner 26F may be configured to adjust the current flowing through each transmitter antenna (e.g., first transmitter antennas 32, 132, 232, 332, second transmitter antennas 134, 234, 334, or third transmitter antenna 336) and the potential applied to each transmitter antenna (e.g., first transmitter antennas 32, 132, 232, 332, second transmitter antennas 134, 234, 334, or third transmitter antenna 336).

[0207] If the current is to pass through both the first transmitter antenna 132 and the second transmitter antenna 134, they each generate a magnetic field 31A for the IPT. If the current supplied to the second transmitter antenna 134 is less than the current supplied to the first transmitter antenna 132, a potential difference is generated between the first transmitter antenna 132 and the second transmitter antenna 134, generating an electric field 31B for the CPT. The current supplied to the second antenna 134 may be modulated to modulate between the CPT and the IPT (for example, if less current passes through the second antenna 134, the IPT will be less, and if more current passes through the second antenna 134, the CPT will be greater). For example, if it is desired to transmit power through the IPT, the I / V tuner 26F may be configured to act as a short circuit connecting the first and second transmitter antennas together, thereby creating a series LC resonator that allows current to flow through it. Conversely, if it is desired to transmit power by CPT, the I / V tuner 26F may be configured to function as an open circuit that dumps current, thereby generating a potential difference between the first transmitter antenna and the second transmitter antenna. Thus, the I / V tuner 26F may be configured to control whether the first transmitter antenna 132 and the second transmitter antenna 134 are effectively connected in series or parallel.

[0208] Alternatively, if the first transmitter antenna 132 and the second transmitter antenna 134 are connected in parallel, the first transmitter antenna 132 and the second transmitter antenna 134 may be made floating to generate an electric field 31B for CPT without substantially generating a magnetic field 31A. To change the transmission mode ratio (for example, to modulate between CPT and IPT), the I / V tuner 26F is configured to alternate (by a multiplexer in the I / V tuner 26F, for example) between (1) causing CPT by floating the first transmitter antenna 132 and the second transmitter antenna 134, and (2) causing IPT by driving current through the first transmitter antenna 132 and the second transmitter antenna 134. This alternation may be performed in milliseconds or at a frequency of 10 Hz to 10 kHz. If more time is allocated to floating the first transmitter antenna 132 and the second transmitter antenna 134, the transmission mode ratio will be more biased towards CPT, and if more time is allocated to driving current through the first transmitter antenna 132 and the second transmitter antenna 134, the transmission mode will be more biased towards IPT.

[0209] In some embodiments, element 26 may be a separate element within the transmitter module 20, and in other embodiments, one or more of element 26 may be part of an integrated circuit design.

[0210] Figure 7 is a schematic diagram of a secondary side 14 (shown in Figure 1) comprising a load 70, a receiver resonator 50, and a receiver module 40, according to several embodiments of the present invention.

[0211] The receiver resonator 50 may comprise any of the receiver resonators 50, 150, 250, 350, or any other described herein. The receiver resonator 50 may be configured to capture power at a frequency set by the oscillation signal in the transmitter module 20, for example, a frequency between 1 MHz and 1 GHz, but not limited to these frequencies.In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is approximately 1MHz to 100MHz, approximately 1MHz to 200MHz, approximately 1MHz to 300MHz, approximately 1MHz to 400MHz, approximately 1MHz to 500MHz, approximately 1MHz to 600MHz, approximately 1MHz to 700MHz, approximately 1MHz to 800MHz, approximately 1MHz to 900MHz, approximately 1MHz to 1GHz, approximately 100MHz to 200MHz, approximately 100MHz to 300MHz, approximately 100MHz to Approximately 400MHz, approximately 100MHz to approximately 500MHz, approximately 100MHz to approximately 600MHz, approximately 100MHz to approximately 700MHz, approximately 100MHz to approximately 800MHz, approximately 100MHz to approximately 900MHz, approximately 100MHz to approximately 1GHz, approximately 200MHz to approximately 300MHz, approximately 200MHz to approximately 400MHz, approximately 200MHz to approximately 500MHz, approximately 200MHz to approximately 600MHz, approximately 200MHz to approximately 700MHz, approximately 200MHz to approximately 800MHz, approximately 200MHz to approximately 900MHz, approximately 200MHz to approximately 1GHz, approx. 300MHz-approx. 400MHz, approx. 300MHz-approx. 500MHz, approx. 300MHz-approx. 600MHz, approx. 300MHz-approx. 700MHz, approx. 300MHz-approx. 800MHz, approx. 300MHz-approx. 900MHz, approx. 300MHz-approx. 1GHz, approx. 400MHz-approx. 500MHz, approx. 400MHz-approx. 600MHz, approx. 400MHz-approx. 700MHz, approx. 400MHz-approx. 800MHz, approx. 400MHz-approx. 900MHz, approx. 400MHz-approx. 1GHz, approx. 500MHz-approx. 600MHz These ranges are approximately 500MHz to 700MHz, 500MHz to 800MHz, 500MHz to 900MHz, 500MHz to 1GHz, 600MHz to 700MHz, 600MHz to 800MHz, 600MHz to 900MHz, 600MHz to 1GHz, 700MHz to 800MHz, 700MHz to 900MHz, 700MHz to 1GHz, 800MHz to 900MHz, 800MHz to 1GHz, or 900MHz to 1GHz.In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is approximately 1 MHz, approximately 100 MHz, approximately 200 MHz, approximately 300 MHz, approximately 400 MHz, approximately 500 MHz, approximately 600 MHz, approximately 700 MHz, approximately 800 MHz, approximately 900 MHz, or approximately 1 GHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at least approximately 1 MHz, approximately 100 MHz, approximately 200 MHz, approximately 300 MHz, approximately 400 MHz, approximately 500 MHz, approximately 600 MHz, approximately 700 MHz, approximately 800 MHz, or approximately 900 MHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at most approximately 100 MHz, approximately 200 MHz, approximately 300 MHz, approximately 400 MHz, approximately 500 MHz, approximately 600 MHz, approximately 700 MHz, approximately 800 MHz, approximately 900 MHz, or approximately 1 GHz.

[0212] For some applications, frequencies in the Industrial, Scientific, and Medical (ISM) frequency bands may be preferred. For the purposes of this disclosure, the ISM bands should be understood to be 6.765MHz–6.795MHz, 13.553MHz–13.567MHz, 26.957MHz–27.283MHz, 40.66MHz–40.70MHz, 83.996MHz–84.004MHz, 167.992MHz–168.008MHz, 433.05MHz–434.79MHz, and 886MHz–906MHz. For other applications, frequencies in officially reserved application bands, such as, but not limited to, police communications or military bands, may be preferred. The receiver resonator 50 may be configured to capture power from the magnetic field 31A or the electric field 31B or any combination of these two fields at their respective frequencies.

[0213] The receiver module 40 includes a controller 42. The controller 42 is configured to receive various inputs from sensors 44 (e.g., a receiver power sensor 44A and a load detector 44B) and to output control signals to various elements 46 (e.g., a compensation network 46A, a matching network 46B, a rectifier 46D, a filter 46C, and a load management unit 46E).

[0214] The receiver power sensor 44A can measure power at point 44C (for example, it can measure current and voltage) to determine how much power is being received by the receiver resonator 50.

[0215] The load detector 44B is configured to detect the presence of a load 70. The load detector 44B may be implemented by a physical sensor (e.g., an optical sensor, pressure sensor, infrared sensor, or proximity sensor, but not limited to these) or by appropriate software or firmware. For example, in some embodiments, current and voltage are measured by the load detector 44B at point 44D, for example, to determine the power received by the load 50. If the amount of power measured at point 44D increases above a baseline, the load detector 44B may signal to the controller 42 that a load 70 is present.

[0216] The compensation network 46A may be configured to maintain a desired resonant frequency of the receiver resonator 50 in response to a signal from the controller 42, thereby improving the efficiency of power transmission from the transmitter resonator 30 to the receiver resonator 50. The compensation network 46A may also be the compensation network 26E of the transmitter module 20, which may function substantially similarly.

[0217] The matching network 26D may be configured to adjust the input impedance of the rectifier 46D to match the desired impedance of the resonator 30, thereby achieving maximum power transmission.

[0218] The rectifier 46D may be configured to convert the AC power received by the receiver antenna 50 into DC power and provide it to the load 70.

[0219] The filter 46C may be configured to shape the waveform of the power output from the rectifier 46D according to a signal from the controller 42 in order to improve the overall power efficiency of the receiver module 40.

[0220] The load management unit 46E may be configured to provide the load 70 with appropriate voltage and current, and / or to extract maximum power from the rectifier 46D by adjusting its input impedance (e.g., the output impedance of the rectifier 46D).

[0221] In some embodiments, the load management unit 46E or another component may be configured to communicate (wirelessly or wired) with an external device (e.g., a load 70) to provide appropriate information for data analysis. Such information may include, but is not limited to, the presence of the load 70, the charge level of the load 70, the charge rate of the load 70, the state of the load 70, the current voltage, capacity, and / or the remaining time to charge the load 70. The load management unit 46E may use such information (or relay such information to the controller 42 or controller 22) to, for example, adjust the transmission mode ratio to achieve optimal energy transfer between the primary side 12 and the secondary side 14. The load management unit 46E may provide such information to the user via a display. Such a display may be integrated into one or more of the primary side 12 and the secondary side 14, or may be accessible via software on a mobile device, such as an app on a mobile phone or tablet, which communicates wirelessly (or wired) with the load management unit 46E or the controller 22 or controller 42.

[0222] In some embodiments, component 46 is a separate element within the receiver module 40, while in other embodiments, one or more components 46 are part of an integrated circuit design.

[0223] In some embodiments, the primary side 12 may comprise a plurality of transmitter resonators 30, and / or the secondary side 14 may comprise a plurality of receiver resonators 50. In such embodiments, each of the transmitter resonators 30 and / or the receiver resonators 50 may be controlled in a similar manner. In other embodiments, each of the transmitter resonators 30 and / or the receiver resonators 50 may be controlled individually. For example, in some embodiments, the primary side 12 may rely more heavily on transmitter resonators 30 that have less interference (e.g., from nearby metal bodies) and are not near living organisms, or that transmit power more efficiently, and / or similarly, the secondary side 14 may rely more heavily on receiver resonators 50 that have less interference (e.g., from nearby metal bodies) and are not near living organisms, or that receive power more efficiently. Such control may be provided or facilitated, for example, by communication between the transmitter module 20 and the receiver module 40, and / or between them.

[0224] Figure 9 is a schematic diagram of a rectifier 46D having an integrated phase shifter. In some embodiments, the rectifier 46D comprises individual phase shifters.

[0225] The rectifier 46D may be a switch-mode self-synchronous rectifier (single-ended mode or differential configuration) that can be configured to receive a sine wave (e.g., AC power) from the receiver resonator 50 at a specific resonant frequency. The rectifier 46D may be a differential switch-mode self-synchronous rectifier. The rectifier 46D may capture sufficient power from the receiver resonator 50 so that an electric field, or a magnetic field, or any combination of electric and magnetic fields can be captured by the receiver resonator 50.

[0226] Rectifier 46D has an input 147A (e.g., AC power) that drives an active device 147B (e.g., a transistor) at a frequency set to the resonant frequency, and an output 147D (e.g., DC voltage) across a DC load (used to control the output power, input impedance, and operating region of the active device). This design uses various load terminations to improve performance (e.g., output power and power conversion efficiency). A third harmonic termination 147D is located in a series branch to shape the voltage waveform at the drain node 147E. A second harmonic termination 147F is located in a parallel branch to shape the voltage waveform at the drain node 147E. A first harmonic termination 147G is located in a series branch to shape the voltage waveform at the drain node 147E. The effect of the third harmonic termination may be considered in the second harmonic termination and the first harmonic termination. The effect of the second harmonic termination may be considered in the first harmonic termination.

[0227] In a differential configuration, the AC power source 147A is arranged in series. The AC power source 147A can be a function of the power received by the receiver resonator 50 and the alignment and position of the receiver resonator 50 relative to the transmitter resonator 30. The DC load 147C may be a single-ended load.

[0228] The rectifier 46D may have two phase shifters 147H in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifters 147H adjust the appropriate phase difference between the AC source and the gate signal of transistor 147B. The phase difference between the gate signal and the AC source 147A can change the performance of the self-synchronous rectifier (e.g., power conversion efficiency and the operating range of the transistor). It can also change the input impedance of the self-synchronous rectifier 46D and / or the optimal DC load 147C of the rectifier 46D.

[0229] The rectifier 46D may have two level shifters 147I in a differential configuration (but only one level shifter in a single-ended configuration). The level shifters 147I can adjust the appropriate amplitude of the gate signal of transistor 147B. The amplitude level of the gate signal can change the performance of the self-synchronous rectifier (e.g., power conversion efficiency and the operating range of the transistor).

[0230] The rectifier 46D may be reconfigurable to function as an amplifier. As part of such reconfiguration, the integrated phase shifter 147H and integrated level shifter 147I may be adjusted to allow the rectifier 46D to function as an amplifier based on the inherent amplification and switching capabilities of transistor 147B. This reconfigurability of the rectifier 46D between rectifier and amplifier operation allows the receiver module 40 to be controllably reconfigured between receiver mode and transmitter mode, respectively. Reconfiguration can be performed under command from the controller 42. When the rectifier 46D is reconfigured from rectifier to amplifier, the AC source 147A changes to an AC load 147A. Correspondingly, when the rectifier 46D is reconfigured from rectifier to amplifier, the DC load 147C is reconfigured to a DC source.

[0231] In some embodiments, when the receiver module 40 is in transmitter mode, the compensation network 46A may be configured to modulate the signal provided to the resonator 50 with information, thereby functioning as a source transmit modulator. The information for modulating the signal provided to the resonator 50 may be provided to the compensation network 46A by the controller 42. The information may include control data of the transmitter module 20 destined for the controller 22 via the resonator 30. In some embodiments, when the receiver module 40 is in transmitter mode and the rectifier 46D is configured as an amplifier, the amplifier 46D may function as a modulator for module 40. The modulation used may be any one of amplitude modulation, frequency modulation, phase modulation, and combinations thereof. The information may be modulated on the signal provided to the transmitter resonator 50 in digital or analog form. The information may be modulated to the resonant frequency of the power signal provided to the transmitter resonator 50 by the source transmit modulator. In other embodiments, the information may be modulated to a frequency different from the power transmission frequency. In other embodiments, the information may be modulated to harmonics of the resonant frequency of the power signal provided to the transmitter resonator 50. In yet another embodiment, the resonant frequency of the power signal supplied to the transmitter resonator 50 may be a harmonic of the frequency of the signal on which the information is modulated. The information transmitted in the manner described herein may include, for example, but not limited to, the presence of the load 70, the charge level of the load 70, the power transmission efficiency, the charge rate of the load 70, the state of the load 70, the current voltage, the charge capacity, and the remaining time to charge the load 70.

[0232] Having described how both modules 20 and 40 can be reconfigured between transmitter and receiver modes, and how signals from both modules 20 and 40 can be modulated, it is clear that system 10 in Figure 1 may function as a full-duplex transceiver system for transmitting information in both directions via resonators 30 and 50. System 10 in Figure 1 may also have additional secondary sides similar to the secondary side 14 in Figures 1 and 7. If additional secondary sides are present, the above configuration allows for communication of information between various secondary sides.

[0233] In some embodiments, the primary side 12 and the secondary side 14 may communicate via Bluetooth (e.g., 2.4 GHz) or a signal frequency similar to GPS (e.g., 10 GHz). In some embodiments, there may be an additional unit that can collect data separately and transmit the data in reverse between the primary side 12 and / or the secondary side 14. In some embodiments, WiFi may be used to upload data from the primary side 12 and / or the secondary side 14 to an online portal (e.g., a website or mobile application associated with the primary side 12 and / or the secondary side 14).

[0234] In some embodiments, it may be desirable to transmit power between two receiver modules 40 (e.g., peer-to-peer power transmission). For example, if the battery of a first e-cycle equipped with a first receiver is depleted or low, and a second e-cycle equipped with a second receiver and at least a partially charged battery is nearby, it may be desirable to transmit power from the second e-cycle to the first e-cycle. Such a situation may relate, for example, when there is no transmitter nearby. A function of at least one of the two receiver modules 40 involved in the reconfiguration into a transmitter module enables such peer-to-peer power transmission. Generally, it enables the transfer of power between multiple secondary sides 14.

[0235] In other embodiments, it may be necessary to transmit power in the reverse direction at a specific time, i.e., from the load side to the source side in Figures 1, 6, and 7. Since both modules 20 and 40 can be reconfigured between transmitter and receiver modes, "reverse" power transmission from module 40 to module 20 is possible. Thus, the system enables bidirectional power transmission. Given the fact that devices 26B and 46D in Figures 8 and 9 can be reconfigured to function as amplifiers or rectifiers, respectively, these devices may be collectively referred to as a "differential self-synchronizing high-frequency power amplifier / rectifier." Considering the bidirectional nature of power transmission, both the transmitter resonator 30 and the receiver resonator 50 may be referred to as a "transmitter-receiver resonator," and both modules 20 and 40 may be referred to as a "power transceiver module." Such a configuration is useful in electric vehicles where kinetic energy needs to be converted and transmitted to a battery during braking. Other systems, conditions, and configurations to which such changes in the direction of power transmission apply include, but are not limited to, numerous mobile phones where the battery level changes and this configuration can be used to at least partially recharge each other. In a more common case, if both the transmitting and receiving systems do not have a permanent energy source, such as grid power, they may use bidirectional functionality to transmit energy in either direction.

[0236] In a further embodiment described with respect to Figure 31, a method is provided for a short-range high-frequency method for transmitting power over a power signal at a power signal frequency

[2200] , comprising providing a bimodal resonant short-range high-frequency power transmission system comprising a plurality of power transceiver modules, wherein each of the plurality of power transceiver modules is in wired communication with a transmitter-receiver resonator arranged to exchange power with at least one other of the plurality of power transceiver modules

[2210] , and operating the power transmission system to perform capacitive power transmission and inductive power transmission simultaneously according to an adjustable transmission mode ratio

[2220] .

[0237] Providing a power transmission system

[2210] may include providing a first of a plurality of power transmission / reception modules having a power signal tuner module, and operating the power transmission system

[2420] may include changing the transmission mode ratio by adjusting the power signal tuner module.

[0238] Providing a power transmission system

[2210] may include providing at least one power transmission module among a plurality of power transmission modules that has a modulator and communicates via wire with an associated transmitter-receiver resonator, and operating the power transmission system

[2220] may include exchanging high-frequency signals between the associated transmitter-receiver resonator and the transmitter-receiver resonator that communicates via wire with at least one other of the plurality of power transmission modules, and modulating information into the high-frequency signals being exchanged. If a power load is present at the output of one of the plurality of power transmission modules, the information modulated into the signals being exchanged may include, for example, but not limited to, the presence of a power load, the charge level of the power load, the power transmission efficiency, the charge rate of the power load, the state of the power load, the presence of a voltage applied to the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0239] The information may be modulated into a high-frequency signal to be exchanged by amplitude modulation, frequency modulation, or phase modulation. Modulating the information into a high-frequency signal to be exchanged may include modulating digital information or analog information into a high-frequency signal to be exchanged.

[0240] Modulating a high-frequency signal to which information is exchanged may include modulating the information into a power signal. Modulating a high-frequency signal to which information is exchanged may also include modulating the information into a signal having a frequency different from the power signal frequency. Modulating a high-frequency signal to which information is exchanged may also include modulating the information into a signal having a frequency that is a harmonic of the power signal frequency. Modulating a high-frequency signal to which information is exchanged may also include modulating the information as a harmonic into a signal having the power signal frequency.

[0241] Modulating a high-frequency signal on which information is exchanged may include, according to the information, modulating the reflection characteristics of the associated wire-connected transmitter-receiver resonator to impose the information on the signal reflected by the wire-connected transmitter-receiver resonator. Modulating a high-frequency signal on which information is exchanged may also include, according to the information, modulating the signal provided to the associated transmitter-receiver resonator.

[0242] This method

[2200] may include operating a power signal tuner module of a first of a plurality of power transceiver modules to modulate a high-frequency signal to which information is exchanged. Each of the power transceiver modules provided may include a compensation network, the compensation network may include a modulator to operate the compensation network so as to modulate a high-frequency signal to which information is exchanged. At least one of the power transceiver modules may include a high-frequency oscillator that provides a signal at a power signal frequency to at least one power transceiver module, the high-frequency oscillator may include a modulator so as to modulate in the oscillator a high-frequency signal to which information is exchanged.

[0243] Each of the multiple power transceiver modules provided may be reconfigurable between a power transmitter mode and a power receiver mode, and this method may further include reconfiguring at least two of the multiple power transceiver modules between a power transmitter mode and a power receiver mode to reverse the direction of power transmission between at least two transceiver modules. Each of the power transceiver modules provided may include a differential self-synchronizing high-frequency power amplifier / rectifier that can be reconfigured between an amplifier state and a rectifier state corresponding to the power transmitter mode and power receiver mode of the power transceiver module, and this method may include reconfiguring the differential self-synchronizing high-frequency power amplifier / rectifiers of at least two transceiver modules between an amplifier state and a rectifier state. Each differential self-synchronizing high-frequency power amplifier / rectifier may include an adjustable phase shifter for reconfiguring the differential self-synchronizing high-frequency power amplifier / rectifier between an amplifier state and a rectifier state, and this method may include adjusting the respective phase shifters of the differential self-synchronizing high-frequency power amplifier / rectifiers of at least two transceiver modules.

[0244] The WPT system 10, including the transmitters and / or receivers described herein, may be integrated into a variety of applications, but are not limited to, electric vehicles, electric boats, electric airplanes, electric trucks, e-bikes, electric scooters, and electric skateboards. One exemplary, non-limiting application is a group of bike-sharing vehicles, where various docking stations are provided, each integrating one or more transmitters (e.g., primary side 12), and e-bikes, equipped with receivers (e.g., secondary side 14) and batteries (as load 70), can be charged at the docking stations.

[0245] In some applications, the primary side 12 or secondary side 14 may be configured to transmit power to other systems not described herein, and even if not specifically designed to operate with the power transmission systems described herein, the transmission mode ratio from CPT to IPT can be adjusted to provide compatibility with other CPT and / or IPT systems.

[0246] Numerous exemplary embodiments and designs have been discussed above, but those skilled in the art will recognize certain modifications, substitutions, additions, and subcombinations thereof. Therefore, the claims subsequently appended and those introduced thereafter are intended to be construed as including all such modifications, substitutions, additions, and subcombinations, in accordance with the broadest interpretation of the entire specification.

[0247] In the first embodiment, each of the systems described above and shown in Figures 1 to 10 is a bimodal short-range resonant wireless power transmission system 10 configured to simultaneously perform capacitive power transmission and inductive power transmission according to an adjustable transmission mode ratio at a variable resonant power signal oscillation frequency, comprising a transmitter subsystem 12 including transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 and a power signal tuner module 26F, wherein the tuner module 26F transmits The system 10 comprises a transmitter subsystem 12 configured to adjust the transmission mode ratio by adjusting the power signals supplied to transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, and 336, and a receiver subsystem 14 comprising receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, and 356 configured to receive power from transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, and 336 in a transmission mode ratio.

[0248] The tuner module 26F may be configured to adjust the power signal by adjusting the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336. The transmitter subsystem 12 may further include a controller 22 and at least one sensor 24. The controller 22 is configured to receive sensor information from the at least one sensor 24 and automatically provide a tuning command to the tuner module 26F based on the sensor information. The tuner module 26F is configured to adjust the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 according to the tuning command.

[0249] System 10 resonates at a resonant frequency that freely varies within a predetermined band based on the degree of coupling between the transmitter subsystem 12 and the receiver subsystem 14. The predetermined band may be, for example but not limited to, an officially designated reserved industrial, scientific, medical (ISM) band, or a specific user - dedicated band. The quality factor (Q) of system 10 may be decreased to the extent that the power signal oscillation frequency can vary within both ends of the predetermined frequency band. As the value of Q decreases, system 10 becomes capable of using any one of a number of different resonant frequencies within the predetermined frequency band during the power transmission process. The coupling between the transmitter subsystem 12 and the receiver subsystem 14, and the absorption of the associated power by the resonant receiver subsystem 14 ensure that there is little electromagnetic radiation emitted into the far - field domain when system 10 is operating. The configurations described herein with reference to FIGS. 1 - 10, together with the immediately preceding frequency aspects, make system 10 a bimodal near - field resonant wireless power transfer system. Note that in the wireless power transfer system 十, power is transmitted from the primary subsystem to the secondary subsystem via capacitive coupling or inductive coupling or both, rather than substantially via electromagnetic radiation.

[0250] In a further aspect described with reference to the foregoing drawings and the flowchart of FIG. 11, a short-range wireless method

[1000] for transmitting power bimodally according to a transmission mode ratio adjustable at the resonant power signal oscillation frequency, comprising providing a transmitter subsystem 12 comprising a power signal tuner module 26F and transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 configured to resonate at a variable resonant power signal oscillation frequency

[1010] ; providing a receiver subsystem 14 comprising receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356 configured to resonate at the resonant power signal oscillation frequency

[1020] ; providing a power signal from the tuner module 26F to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 at the power signal oscillation resonant frequency

[1030] ; adjusting the transmission mode ratio by adjusting the power signal from the tuner module 26F to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336

[1040] ; and in the receiver subsystem 14, receiving the transmitted power at the power signal oscillation resonant frequency via the receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356 at the transmission mode ratio

[1050] . Adjusting the transmission mode ratio

[1040] may include adjusting the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336.

[0251] Providing the transmitter subsystem 12

[1010] may further include providing a controller 22 and at least one sensor 24, and adjusting the phase difference between current and voltage may be performed by the tuner module 26F via a command of the controller 22 based on sensor information received by the controller 22 from at least one sensor 24. A command of the controller 22 may be automatically issued to the tuner module 26F when the controller 22 receives sensor information, and the tuner module 26F may automatically execute the command from the controller 22 to change the phase difference.

[0252] This method

[1000] may further include making the resonant power signal oscillation frequency variable within a predetermined frequency band

[1060] . The predetermined frequency band may be an industrial, scientific, or medical (ISM) frequency band. Providing a transmitter subsystem

[1010] may include providing a transmitter subsystem that is detuned to such an extent that the resonant power signal oscillation frequency can be varied across both ends of the predetermined frequency band.

[0253] In further embodiments described with reference to Figures 12, 13A, and 13B, and also with reference to Figures 1-10, the multi-transmitter bimodal short-range resonant wireless power transmission system 10' is configured to simultaneously perform capacitive and inductive power transmission according to an adjustable transmission mode ratio at a variable resonant power signal oscillation frequency. System 10' comprises a multi-transmitter subsystem 12' having a plurality of transmitter resonators 30A'-30I', each driven by corresponding dedicated transmitter modules 20A'-20I', respectively, where each transmitter resonator and corresponding transmitter module (e.g., 30E' and 20E', respectively) may correspond to the description given above with reference to Figures 1-10. Figure 12 is a schematic diagram of one embodiment of system 10', where the transmitter resonators 30A'-30I' are shown as nine resonators in tandem, but their formal spatial positions are not shown. One embodiment of the spatial layout of the multi-transmitter subsystem 12' is shown in Figures 13A and 13B and described below. In system 10', the resonant receiver subsystem 14 may be identical or substantially similar to the resonant receiver system described above and referenced by Figures 1-10. In the embodiment shown in Figure 12, the resonant receiver subsystem 14 may be implemented in, for example, a mobile phone or a digital "tablet". For clarity, the resonant receiver subsystem 14 is shown by a dashed line in Figure 13A. In one embodiment, each operating transmitter resonator 30A'-30I' and each corresponding transmitter module 20A'-20I' may function in the same or substantially similar manner as the transmitter resonator 30 and transmitter module 20 described above and shown in Figures 1-10. One embodiment of the spatial layout of the multi-transmitter subsystem 12' is shown in Figures 13A and 13B. Figure 13B is a diagram of the multi-transmitter subsystem 12' oriented in the opposite direction to that in Figure 13A.

[0254] In exemplary embodiments of system 10' shown in Figures 12, 13A, and 13B, the multi-transmitter subsystem 12' comprises nine pairs of transmitter resonators 30A'~30I' and corresponding transmitter modules 20A'~20I' arranged in a square array. The transmitter modules 20A'~20I' are hidden in Figure 13A by a grounded base plate 35' but are visible in Figure 13B. In more general embodiments, other numbers of pairs of resonators and transmitter modules may be used, and the resonator array does not have to be square or rectangular. In non-limiting examples, the resonator array may have a hexagonal arrangement. In some embodiments, the array is preferably close-packed within the constraint of having a grounded shield grid that separates and boundaries the transmitter resonators 30A'~30I'. The grounded shield grid 33' laterally confines the array of transmitter resonators 30A'~30I'. The grounding shield grid 33' is positioned at a constant distance 37' from each of the transmitter resonators 30A'~30I' to ensure consistent electric field behavior and associated capacitance between the transmitter resonators 30A'~30I' and the grounding shield grid 33'. The term "shielding distance" is used herein to describe this distance between the resonators 30A'~30I' and the grounding shield grid 33'.

[0255] In one embodiment, the grounding shield grid 33' ensures that the electric fields of the transmitter resonators 30A'~30I' are completely spatially isolated and thus spatially independent. The transmitter resonators 30A'~30I' may have magnetic fields selected to be isolated from each other by spatial orientation. In another embodiment, the grounding shield grid 33' may be formed or coated with a highly conductive ferrite material to isolate the magnetic fields generated by the transmitter resonators 30A'~30I'.

[0256] As shown in Figures 13A and 13B, the transmitter resonators 30A' to 30I' and their corresponding transmitter modules 20A' to 20I' may be mounted substantially in rows on both sides of the ground base plate 35', with each transmitter resonator (e.g., 30E') in close proximity to its corresponding transmitter module (20E'). In other embodiments, there may be no fixed spatial relationship between the transmitter resonators and their corresponding transmitter modules. The array of transmitter resonators 30A' to 30I' shares a common transmitting surface defined by the collective upper surface of the transmitter resonators 30A' to 30I' in Figure 13A. For aesthetic and protective reasons, the array of transmitter resonators 30A' to 30I' may be covered with a dielectric plate, which is not shown in Figure 13A. The dielectric plate separates the receiver subsystem 14 from the transmitter resonators 30A' to 30I'.

[0257] Figures 12 and 13A schematically show one embodiment of the resonant receiver subsystem 14 overlapping a subset of several transmitter resonators 30A' to 30I'. According to Figures 12 and 13A, the overlapping transmitter resonators are shown as 30D', 30E', ​​30G', and 30H'. In Figure 13A, the resonant receiver subsystem 14 is shown as dashed rectangles on the mutually adjacent transmitter resonators 30D', 30E', ​​30G', and 30H'. A controller of any of the transmitter modules 20A' to 20I' may determine the presence or absence of a resonant receiver subsystem 14 adjacent to or overlapping their corresponding transmitter resonators 30A' to 30I', and based on these detections, the controller may turn on or turn on power signals to the corresponding transmitter resonators 30A' to 30I'.

[0258] If the power amplifiers of transmitter modules 20A'~20I' supply power signals to the transmitter resonators 30A'~30I' so that the transmitter resonators 30A'~30I' transmit power, and the controllers of transmitter modules 20A', 20B', 20C', 20F', and 20I' determine that there are no resonant receivers within their frequency ranges adjacent to the transmitter resonators 30A', 30B', 30C', 30F', and 30I', then these controllers may turn off the power signals to the transmitter resonators 30A', 30B', 30C', 30F', and 30I.

[0259] If the power amplifiers of transmitter modules 20A'~20I' are not supplying power signals to transmitter resonators 30A'~30I', the controllers of transmitter resonators 30D', 30E', ​​30G', and 30H' can determine the presence of a resonant receiver subsystem 14 that overlaps with and is adjacent to the resonators 30D', 30E', ​​30G', and 30H', and can turn on the transmittable power supplied to the transmitter resonators 30D', 30E', ​​30G', and 30H' by transmitter modules 20D', 20E', 20G', and 20H'. This configuration ensures that only the transmitter resonators adjacent to the resonant receiver subsystem 14 consume power and transmit power to the resonant receiver subsystem 14.

[0260] The presence or absence of a resonant receiver subsystem 14 adjacent to a specific transmitter resonator may be detected using the input impedance of a particular transmitter resonator 30A'~30I'. The input impedance of the transmitter resonator changes depending on the presence or absence of the resonant receiver subsystem 14 adjacent to the particular transmitter resonator. As described above with reference to Figure 6, the effect of the particular resonant receiver subsystem 14 is clear in that it not only allows for the detection of the presence or absence of the receiver, but is also characteristic enough to allow for the identification of the type of receiver by its effect on the input impedance of the transmitter resonator. In particular, the size of the receiver resonator has a significant effect on the input impedance of the particular transmitter resonator 30A'~30I'.

[0261] In one embodiment of system 10', transmitter module 20E' is a transmitter module associated with one of four transmitter resonators 30D', 30E', ​​30G', and 30H' that overlap with the resonant receiver subsystem 14, as shown in Figures 12 and 13B. The detailed structures of each of the transmitter modules 20A' to 20I' are provided in Figures 6 and 8. The process is initiated by the power amplifier 26B of the transmitter modules 20A' to 20I', which do not supply power signals to the corresponding transmitter resonators 30A' to 30I'.

[0262] Focusing on the transmitter module 20E', its load detector 24A in this embodiment is configured to measure the input impedance of the transmitter resonator 30E'. The load detector 24A provides the input impedance measurement result to the controller 22. The default input impedance measurement value represents the input impedance of the transmitter resonator 30E' when there is no resonant receiver subsystem adjacent to the transmitter resonator 30E', ​​and is stored in a register in the controller 22. As shown in Figure 12, the placement of the resonant receiver subsystem 14 adjacent to the transmitter resonator 30E' results in a new and different input impedance measurement value by the load detector 24A, which is supplied to the controller 22 by the load detector 24A. The controller 22 compares the new input impedance measurement value, referred to herein as the "first input transmitter resonator impedance change" or "primary transmitter resonator input impedance change," with the default impedance measurement value stored in the register. Based on this first input impedance change, the controller 22 makes a determination as to whether a receiver resonator, for example, the resonator of the resonant receiver subsystem 14, is located adjacent to the transmitter resonator 30E'. To determine the presence or absence of a receiver resonator adjacent to the transmitter resonator 30E', ​​the controller 22 may be pre-programmed with a minimum input impedance change that must be exceeded before the controller 22 determines that a receiver resonator is present.

[0263] If the controller 22 determines that a receiver resonator, for example, the resonator of the resonant receiver subsystem 14, is located in close proximity to the transmitter resonator 30E', ​​the controller 22 commands the power amplifier to enter an "on" state. This supplies power to the transmitter resonator 30E', ​​which is then transmitted to the resonant receiver subsystem 14. If the controller 22 determines that a receiver resonator, for example, the resonator of the resonant receiver subsystem 14, is not located in close proximity to the transmitter resonator 30E', ​​the controller 22 commands the power amplifier to enter an "off" state. This prevents power from being supplied to the transmitter resonator 30E', ​​and therefore prevents power from being transmitted to the resonant receiver subsystem 14. The same process is performed independently by all transmitter modules 20A' to 20I' for the corresponding transmitter resonators 30A' to 30I'. As a result, the power amplifiers of transmitter modules 30D', 30E', ​​30G', and 30H' that overlap with the resonant receiver subsystem 14 are turned on, while the power amplifiers of transmitter modules 30A', 30B', 30C', 30F', and 30I' that do not overlap with the resonant receiver subsystem 14 are turned off.

[0264] It should be noted that receiver resonators of different sizes exhibit significantly different impedances to the load detector 24A of the transmitter module 20 at point 24A. The impedance difference measured when a given receiver resonator partially overlaps with a particular transmitter resonator is not as dramatically different as the impedance difference due to the size of the receiver resonator compared to when it completely overlaps with the transmitter resonator. This allows the controller 22 of the transmitter modules 20A'~20I' to distinguish between small and large receiver resonators adjacent to the corresponding transmitter resonators 30A'~30I'.

[0265] According to one embodiment, the setting of power signal frequencies and phases between a resonant receiver subsystem, for example, a resonant receiver subsystem 14, and overlapping transmitter resonators (e.g., 30D', 30E', ​​30G', and 30H') is described herein. For the most efficient transmission of power from the combination of transmitter resonators 30D', 30E', ​​30G', and 30H' receiving power, the power signals in the resonators 30D', 30E', ​​30G', and 30H' must have the same frequency and be in phase with each other. Given that the frequencies of the power signals in the transmitter resonators 30D', 30E', ​​30G', and 30H' may differ within the allowable bandwidth, as previously described with reference to Figures 1-10, the requirement in this embodiment of Figures 12, 13A, and 13B is that the frequencies of the power signals in the transmitter resonators 30D', 30E', ​​30G', and 30H' are adjusted to be identical and their phases then locked together, so that the power signals from the transmitter resonators 30D', 30E', ​​30G', and 30H' are perfectly synchronized and in phase.

[0266] In one embodiment, to ensure that all controllers 22 of the overlapping transmitter resonators 30D', 30E', ​​30G', and 30H' set their corresponding oscillators 26A to the same frequency, all controllers 22 of transmitter modules 20A' to 20I' are provided with the same frequency table selected within an arbitrary allowable bandwidth, e.g., the ISM bandwidth. Within that particular ISM bandwidth, a number of discrete frequencies are selected to be included in the frequency table. Thus, the number of aggregated frequencies within that ISM bandwidth is finite and limited, and the aggregated frequencies are spaced far enough apart that the various controllers 22 of the transmitter modules 20D', 20E', 20G', and 20H' can determine the power signal frequency from the aforementioned impedance differences. Despite these small variations in impedance, all controllers 22 of the transmitter modules 20D', 20E', 20G', and 20H' select the same discrete frequency from the allowable frequencies within the bandwidth for the power signals of their respective oscillators 26A and power amplifiers 26B.

[0267] In one embodiment, the following procedure is employed and programmed into the software of each controller 22 of transmitter modules 20A' to 20I' to ensure that all resonators 30D', 30E', ​​30G', and 30H' have the same power signal frequency as well as the same phase. Statistically, the first of the independent controllers 22 of transmitter modules 20D', 20E', 20G', and 20H' first turns on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second of the other independent controllers 22 of the controllers of transmitter modules 20D', 20E', 20G', and 20H' measures the input impedance of its corresponding transmitter resonator and detects a small second-order change in its impedance due to the function of the first transmitter resonator using its corresponding load detector 24A. In practice, the second controller 22 observes the effect of the impedance of the first transmitter resonator through its interaction with the latter and the resonant receiver subsystem 14. The second controller 22 is programmed to determine, based on the change in the secondary impedance, that another controller initially turned on its oscillator 26A and power amplifier 26B. Having made this conclusion, the second controller 22 turns on its oscillator 26A and power amplifier 26B and measures the power transmitted by its corresponding transmitter resonator using its transmitter power sensor 24B while changing the phase of its power signal. The second controller 22 then changes the phase of its oscillator to search for the phase at which maximum power transmission occurs and sets the oscillator phase to that value. The oscillator phase thus determined ensures that the phase of the power signal transmitted by the second transmitter resonator is equal to the phase of the power signal transmitted to the resonant receiver subsystem 14 by the first transmitter resonator. In one embodiment, the setting of the oscillator phase is based on substantially maximizing power transmission rather than completely equalizing the power signal phases.

[0268] In another embodiment, based on the fact that the transmitter resonators 30D', 30E', ​​30G', and 30H' overlap with the resonant receiver subsystem 14, proximity detection of the resonant receiver subsystem 14 is based on the test signal power consumed through the transmitter resonators 30D', 30E', ​​30G', and 30H'. In this embodiment, the low-amplitude power signal is first maintained by oscillators and power amplifiers corresponding to all of the transmitter resonators 30A' to 30I'. Then, the controllers 22 of all the transmitter modules 20A' to 20I' use their corresponding transmitter power sensors 24B to detect the power consumed by their corresponding transmitter resonators 30. Using their corresponding transmitter power sensors 24B, the controllers 22 of the transmitter modules 20D', 20E', 20G', and 20H' detect that power is being drawn through their corresponding transmitter resonators 30D', 30E', ​​30G', and 30H'. Based on the detection of consumed test signal power, the controllers 22 of the transmitter modules 20D', 20E', 20G', and 20H' turn on the full power of their corresponding power amplifiers 26B. The term “consumption of initial test signal power” is used herein to describe this power consumed from the test signal through the transmitter resonators 30D', 30E', ​​30G', and 30H'. The test power signals of the power amplifiers 26B of the transmitter modules 30A', 30B', 30C', 30F', and 30I' that do not overlap with the resonant receiver subsystem 14 may be turned off after a suitable test period.

[0269] Similar to the impedance-based embodiments described above, the controller 22 of the transmitter modules 20D', 20E', 20G', and 20H' may require a threshold power consumption in order to consider the resonant receiver subsystems 14 to be located in close proximity to their corresponding transmitter resonators 30D', 30E', ​​30G', and 30H'.

[0270] In one embodiment, to ensure that all controllers 22 of the overlapping transmitter resonators 30D', 30E', ​​30G', and 30H' set their corresponding oscillators 26A to the same frequency, all controllers 22 of transmitter modules 20A' to 20I' are provided with the same frequency table selected within an arbitrary allowable bandwidth, e.g., the ISM bandwidth. Within that particular ISM bandwidth, a number of discrete frequencies are selected to be included in the frequency table. Thus, the number of aggregated frequencies within that ISM bandwidth is finite and limited, and the aggregated frequencies are spaced far enough apart that the various controllers 22 of the transmitter modules 20D', 20E', 20G', and 20H' can determine the power signal frequency from the consumption of the initial test signal power described above. Despite small fluctuations in these power consumption values, all controllers 22 in transmitter modules 20D', 20E', 20G', and 20H' select the same discrete frequency from the allowable frequencies within the bandwidth for the power signals of their respective oscillators 26A and power amplifiers 26B.

[0271] In one embodiment, to ensure that all of the resonators 30D’, 30E’, 30G’, and 30H’ have not only the same power signal frequency but also the same phase, the following procedure is adopted and programmed into the software of each controller 22 of the transmitter modules 20A’ to 20I’. Statistically, the first of the independent controllers 22 of the transmitter modules 20D’, 20E’, 20G’, and 20H’ first turns on its corresponding oscillator 26A and power amplifier 26B and supplies power to the resonant receiver subsystem 14 via its transmitter resonator. The second of the other independent controllers 22 of the transmitter modules 20D’, 20E’, 20G’, and 20H’ measures the power consumption of its corresponding transmitter resonator and detects, by its corresponding transmitter power sensor 24B, a small secondary change in that power consumption due to the function of the first transmitter resonator. In practice, the second controller 22 looks at the influence of the impedance of the first transmitter resonator via the interaction of the latter with the resonant receiver subsystem 14. The second controller 22 is programmed to determine, based on the secondary change in power consumption, that another controller first turned on its oscillator 26A and power amplifier 26B. After reaching this conclusion, the second controller 22 turns on its oscillator 26A and power amplifier 26B and uses its transmitter power sensor 24B to measure the power transmitted by its corresponding transmitter resonator while varying the phase of its power signal. Next, the second controller 22 searches for the phase at which maximum power transmission occurs and sets the oscillator to that phase. The oscillator phase thus set ensures that the phase of the power signal transmitted by the second transmitter resonator to the resonant receiver subsystem 14 is equal to the phase of the power signal transmitted by the first transmitter resonator to the resonant receiver subsystem 14. In this embodiment, the setting of the oscillator phase is based on substantially maximizing power transmission rather than completely equalizing the power signal phases.

[0272] In one embodiment, if two different resonant receiver subsystems are adjacent to a multi-transmitter subsystem 12' and overlap with one or a different combination of transmitter resonators 30A'~30I', there is no prior reason, nor is there a need, for the two different transmitter resonators, or two different groups of transmitter resonators overlapping with two resonant receiver systems, to operate at the same frequency or in the same phase. The grounded shield grid 33' ensures this multidirectional independence by isolating all of the individual transmitter resonators 30A'~30I' from one another. However, the transmitter resonators overlapping with one particular resonant receiver subsystem must have their corresponding power signal amplifiers actively synchronized by their controllers, as described above. This allows two different transmitter resonators or two different groups of resonators to operate at two specific different lock-in frequencies within the band, and all signals within a particular group to be in phase with each other.

[0273] The above described how two transmitter resonators transmitting power to the same receiver resonator can be programmed to operate so that the two transmitter resonators carry in-phase power signals, thereby ensuring maximum power transmission. A different situation arises when two adjacent transmitter resonators, for example 30A' and 30B' in Figure 14, are transmitting to two substantially similar corresponding receiver subsystems 14A and 14B. Both transmitter resonators 30A' and 30B' have fringe fields where field (electric / magnetic field) lines extend, for example, from transmitter resonator 30A' to receiver subsystem 14B' and from transmitter resonator 30B' to receiver subsystem 14A. In general, system 10' does not have any specific physical structure to prevent, for example, the field (electric / magnetic field) of transmitter resonator 30A' from interacting with the receiver resonator of receiver subsystem 14B.

[0274] In one embodiment, when both transmitter resonators 30A' and 30B' function as the same large receiver resonator overlapping with both transmitter resonators 30A' and 30B' (as shown in Figure 13A), the fringe field is essentially not a problem because both transmitter resonators 30A' and 30B' operate with power signals of the same frequency in the same phase. In the situation shown in Figure 14, the requirement is to ensure that power from transmitter resonator 30A' is not parasitic due to any fringe field of a given transmitter resonator, e.g., 30A', interacting with a receiver subsystem (e.g., receiver subsystem 14B intended to receive power from an adjacent transmitter resonator 30B'). One way to achieve this goal is to drive two adjacent transmitter resonators 30A' and 30B' with a 180° phase difference from each other such that most of the overlapping fringe fields from the transmitter resonators 30A' and 30B' cancel each other out.

[0275] Since one of the transmitter resonators 30A' and 30B' parasitically receives the other of the transmitter resonators 30A' and 30B' if their power signals are not out of phase by 180°, the controllers 22 for each of the transmitter resonators 30A' and 30B' may increment the phase of the signals from their respective oscillators while measuring the power transmitted by the corresponding transmitter resonators 30A' and 30B' using the corresponding transmitter power sensor 24B. The controllers 22 may then search for an adjusted oscillator phase that provides the maximum transmit power through the corresponding transmitter resonators 30A' and 30B' and set the oscillator phase to its corresponding phase.

[0276] As described above, the frequency and phase arrangement for each resonant receiver system, whether of the same or different sizes, ensures that both resonant receiver systems receive maximum transmission power. In a typical embodiment, there may be multiple transmitter resonators, and several different resonant receiver subsystems may receive power, each resonant receiver subsystem receiving power from its own corresponding individual group of transmitter resonators at frequencies and phases selected by controllers corresponding to the transmitter resonators in the group. Adjacent transmitter resonators transmitting power to different receiver subsystems may operate with a 180° phase shift as a result of maximizing the power transmission of each adjacent transmitter resonator. The process of maximizing power transmission adjusts the phase of the oscillators. Because the impedances of various transmitter modules are complex and their resistance, inductance, and capacitance vary slightly, the phase angles of different oscillators at the point of maximum power transmission do not have to be exactly equal (or exactly 180° different) if the power signals in the transmitter resonators are actually equal (or exactly 180° different).

[0277] As long as system 10' comprises a single circuit having an air gap between the primary and secondary sides, any power transmission measured or maximized in the transmitter resonator at point 24E in Figure 6, for example, based on measurements by the transmitter power sensor 24B, can also be measured or maximized in the secondary circuit at point 44C in Figure 7, for example, based on measurements by the receiver power sensor 44A. The measurements may also be provided to the controller 42 of the receiver module 40 by the transmitter power sensor 24B, and the receiver module 40 may transmit the measurements to the controller 22 of the transmitter module 20 by one of the means described above.

[0278] The concept of a multi-transmitter short-range resonant wireless power transmission system was described above with reference to system 10', which is configured to simultaneously perform capacitive and inductive power transmission according to an adjustable transmission mode ratio at a variable resonant power signal oscillation frequency. In a more general embodiment, the multi-transmitter short-range resonant wireless power transmission system does not necessarily have to be a bimodal system, and may be a purely capacitive power transmission system or a purely inductive power transmission system.

[0279] In a further embodiment, as shown in the flowchart of Figure 15, a wireless short-range method

[1100] for transmitting power from a multi-transmitter subsystem 12' to a single resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency comprises a plurality of mutually independent transmitter resonators 30A'~30I', each of which is driven by a corresponding transmitter module 20A'~20I', each transmitter module 20A'~20I' can be independently set to one of a plurality of preset power signal oscillation frequencies within a preset frequency band, and all transmitter resonators 30A'~30I' have a common transmitting surface. The present invention includes providing a multi-transmitter subsystem 12' equipped with resonators 30A' to 30I'

[1110] , arranging a resonant receiver subsystem 14, which has a single receiver resonator 50 overlapping with two or more of the transmitter resonators (30D', 30E', ​​30G', and 30H in Figure 13A), in close proximity to the common transmitting plane

[1120] , measuring the input impedance of each of the transmitter resonators 30A' to 30I'

[1130] , and setting the power signals to each of the mutually independent transmitter resonators 30A' to 30I' to either an off state or an active state based on the corresponding measured resonator input impedances

[1140] .

[0280] This method

[1100] may further include selecting the power signal oscillation frequency of the corresponding transmitter resonator (30D', 30E', ​​30G', and 30H' in Figure 13A) from a set of preset power oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (30D', 30E', ​​30G', and 30H' in Figure 13A)

[1150] .

[0281] This method

[1100] may further include setting the power signals of each active transmitter resonator (30D', 30E', ​​30G', and 30H' in Figure 13A) to the corresponding selected frequency

[1160] .

[0282] This method

[1100] may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator (resonators 30D', 30E', ​​30G', and 30H in Figure 13A) to a phase that substantially maximizes power transmission through the transmitter resonators (30D', 30E', ​​30G', and 30H' in Figure 13A)

[1170] .

[0283] In a further embodiment, as shown in the flowchart of Figure 16, a wireless short-range method

[1200] for transmitting power from a multi-transmitter subsystem 12' to a single resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency comprises a plurality of mutually independent transmitter resonators 30A'~30I', each of which is driven by a corresponding transmitter module 20A'~20I', each transmitter module 20A'~20I' can be independently set to one of a plurality of preset power signal oscillation frequencies within a preset frequency band, and all transmitter resonators 30A'~30I' have a common transmitting surface. The invention includes providing a multi-transmitter subsystem 12' comprising A'~30I'

[1210] , arranging a resonant receiver subsystem 14 having a single receiver resonator 50 overlapping with two or more of the transmitter resonators (30D', 30E', ​​30G', and 30H in Figure 13A) in close proximity to the common transmitting plane

[1220] , measuring the power consumed from the test signal by each of the transmitter resonators 30A'~30I'

[1230] , and setting the power signals to each of the mutually independent transmitter resonators 30A'~30I' to either an off state or an active state based on the measured test power consumption of the corresponding resonators

[1140] .

[0284] This method

[1200] may further include selecting the power signal oscillation frequency of the corresponding transmitter resonator (30D', 30E', ​​30G', and 30H in Figure 13A) from a set of preset power oscillation frequencies based on the measured test signal consumption of each of the active transmitter resonators (30D', 30E', ​​30G', and 30H in Figure 13A)

[1250] .

[0285] This method

[1200] may further include setting the power signals of each active transmitter resonator (30D', 30E', ​​30G', and 30H in Figure 13A) to the corresponding selected frequencies

[1260] .

[0286] This method

[1200] may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator (resonators 30D', 30E', ​​30G', and 30H in Figure 13A) to a phase that substantially maximizes power transmission through the transmitter resonators (30D', 30E', ​​30G', and 30H in Figure 13A)

[1270] .

[0287] In a further embodiment, as shown in the flowchart of Figure 17, a wireless short-range method

[1300] for transmitting power from a multi-transmitter subsystem 12' to two or more resonant receiver subsystems 14A, 14B (Figure 14) at a variable resonant power signal oscillation frequency comprises a plurality of mutually independent transmitter resonators 30A'~30I' (Figure 14), each of which is driven by a corresponding transmitter module 20A'~20I' (see Figure 13B), each transmitter module 20A'~20I' being independently set to one of a plurality of preset power signal oscillation frequencies within a preset frequency band, and all transmitter resonators 30A'~30I' having a common transmitting surface, The present invention includes providing a multi-transmitter subsystem 12' having several transmitter resonators 30A' to 30I'

[1310] , arranging two or more resonant receiver subsystems 14A, 14B (Figure 14), each having a single receiver resonator overlapping with one or more of the transmitter resonators (transmitter resonators 30A', 30B' in Figure 14), in close proximity to a common transmitting plane

[1320] , measuring the input impedance of each of the transmitter resonators 30A', 30B'

[1330] , and setting the power signals to each of the mutually independent transmitter resonators 30A' to 30I' to either an off state or an active state based on the corresponding measured resonator input impedances

[1340] .

[0288] This method

[1300] may further include selecting the power signal oscillation frequency of the corresponding transmitter resonators 30A', 30B' from a set of preset power oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (resonators 30A', 30B' in Figure 14)

[1350] .

[0289] This method

[1300] may further include setting the power signals of each active transmitter resonator 30A', 30B' to the corresponding selected frequency

[1360] .

[0290] This method

[1300] may further include adjusting the phase of the power signals applied to each corresponding transmitter resonator 30A', 30B' to a phase that substantially maximizes power transmission through the transmitter resonators 30A', 30B' (Figure 14)

[1370] .

[0291] In a further embodiment, as shown in the flowchart of Figure 18, a wireless short-range method

[1400] for transmitting power from a multi-transmitter subsystem 12' to two or more resonant receiver subsystems 14A, 14B (Figure 14) at a variable resonant power signal oscillation frequency comprises a plurality of mutually independent transmitter resonators 30A'~30I' (Figure 14), each of which is driven by a corresponding transmitter module 20A'~20I' (see Figure 13B), each transmitter module 20A'~20I' being independently set to one of a plurality of preset power signal oscillation frequencies within a preset frequency band, and all transmitter resonators 30A'~30I' having a common transmitting surface, The present invention includes providing a multi-transmitter subsystem 12' equipped with transmitter resonators 30A' to 30I'

[1410] , arranging two or more resonant receiver subsystems 14A, 14B (Figure 14), each having a single receiver resonator that overlaps with one or more of the transmitter resonators (transmitter resonators 30A', 30B' in Figure 13), in close proximity to a common transmitting surface

[1420] , measuring the power consumed from a test signal by each of the transmitter resonators 30A' to 30I'

[1430] , and setting the power signals to each of the mutually independent transmitter resonators 30A' to 30I' to either an off state or an active state based on the consumption of the test signal by the corresponding measured resonator

[1440] .

[0292] This method

[1400] may further include selecting the power signal oscillation frequency of the corresponding transmitter resonators 30A', 30B' from a set of preset power oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (resonators 30A', 30B' in Figure 14)

[1450] .

[0293] This method

[1400] may further include setting the power signals of each active transmitter resonator 30A', 30B' to the corresponding selected frequency

[1460] .

[0294] This method

[1400] may further include adjusting the phase of the power signals applied to the corresponding transmitter resonators 30A', 30B' to a phase that substantially maximizes power transmission through the transmitter resonators 30A', 30B' (Figure 14)

[1470] .

[0295] In further embodiments described with reference to Figures 20A and 20B, Figures 21A and 21B, and Figures 22A and 22B, a short-range resonant wireless power transmission system 10'' for wirelessly transmitting power from a photovoltaic solar cell 420 to a power load 70'' is presented according to the schematic diagram of Figure 19A, based on the systems of Figures 1 to 10 and Figures 12 to 14. The labels in Figure 19A use an accented numbering system so that the similarities with Figures 13A and 13B are clear, and thus the similarities with Figures 6 and 7 are also clear. With this numbering scheme, DC power is supplied from the solar cell 420 to the transmitter module 20'' via a power regulating unit (PCU) 430. The PCU 430 not only converts the DC voltage and DC current to levels that can be further transmitted by a power amplifier 26B'', but also provides appropriately regulated levels of voltage and current to drive the remaining system components in the transmitter module 20'', including small-signal electronic components. The PCU430 represents an adaptively changing load on the solar cell 420 to accommodate the varying power supplied by the solar cell 420 and the varying output impedances presented to the PCU430 by the solar cell 420. This allows the PCU430 to absorb power from the solar cell 420 at the maximum possible rate at any time and temperature, regardless of fluctuations in power from the solar cell 420.

[0296] Oscillator 26A'' may be used to modulate power amplifier 26B'' at a frequency suitable for wireless power transmission, as already described above. Power amplifier 26B'' may have the same design as amplifier 26B shown in Figure 8, but DC power may be supplied from PCU430 instead of as DC voltage 127E. In alternative embodiments, power amplifier 26B'' may appropriately include a circuit that maintains oscillation by itself, as is well known in the field of wireless systems, thereby eliminating the need for oscillator 26A''.

[0297] Power may be transmitted to the transmitter resonator 30'' via the transmitter tuning network 28'', which in Figure 19A is an integration of the signal conditioning and tuning components 26C, 26D, 26E, and 26F in Figure 6. The transmitter resonator 30'' may have a surface area that can be at least a large portion of the range of the active solar radiation receiving surface of the solar cell 420. Just as the corresponding components of the transmitter module 20 in Figure 6 are under the control of the controller 22'', all these components of the transmitter module 20'' are under the control of the controller 22''. For clarity, not all components of the transmitter module 20'' are shown in Figure 19A. The sensors and detectors 24A, 24B, 24C, and 24D in Figure 6 may also be present in the transmitter module 20'' in an equivalent form and connected to the controller 22'', and may perform the same role as in Figure 6.

[0298] Power can be transmitted wirelessly from the transmitter module 20'' to the receiver module 40'' via the transmitter resonator 30'' and the receiver resonator 50''. Power can then be transmitted from the receiver module 40'' to the DC load 70''. The transmission of power between the transmitter resonator 30'' and the receiver resonator 50'' may be by short-range wireless transmission as described above with reference to Figures 6-10. The short-range wireless power transmission shown in Figure 20 is not limited to bimodal but may be purely capacitive or purely inductive.

[0299] The receiver module 40'' may have the same components as the receiver 40 in Figure 7. For clarity, a reduced set of these components is shown in Figure 19A. The sensors 44A and detectors 44B in Figure 7 are not shown in equivalent form in Figure 19A, but may be present. The receiver tuning network 48'' in Figure 19A may be an integration of the compensation network 46A, matching network 46B, rectifier 46D, and filter 46C. Power is transmitted from the receiver tuning network 28'' to the load management unit 46E'', both of which may be under the control of the receiver controller 42''. With respect to the rectifier 46D shown in detail in Figure 7, the input impedance of this device depends directly on the load on which the output of the device is subjected. During operation, the near-range resonant wireless power transmission system 10'' may function in the same way as the near-range resonant wireless power transmission system 10 in Figures 1 and 6-10, except that the applied voltage V of each power amplifier 26B'' DDThe power signal is replaced by a power signal from a power regulating unit (PCU) 430, which in this embodiment receives its power from an associated power source, which is a solar cell 420. In another embodiment, the power regulating unit 430 may be omitted from the system shown in Figure 19A, and instead the power transmission system 10'' may be configured or operate as a power regulating system as well. This may be achieved by configuring a controller 22'' in software, for example but not limited to adjust the input DC equivalent resistance of the power amplifier 26B'' based on the power level measured by the power sensor 24B in Figure 6. The term “input DC equivalent resistance” is used here to describe the ratio of DC voltage to DC current at the DC terminal of the power amplifier 26B. The controller 22'' makes adjustments based on power measurements, but it is expected that the maximum power point of the power transmitted will be achieved when the input impedance of the power amplifier 26B'' matches the output impedance of the solar cell 420. In this embodiment, system 10'' functions as what is known in industry as a “maximum power point tracking device,” ensuring that power is always transmitted at a rate more suitable to the power-consuming load than would be obtained if the power supply were unregulated. In another embodiment, controller 22'' may be configured to measure the output impedance of a power source, which in this embodiment is a solar cell 420, and then adjust the input impedance of power amplifier 26B'' based on the measured output impedance of solar cell 420. In addition to adjusting the input impedance of power amplifier 26B'', controller 22'' may also adjust one or more of the settings of the transmitter tuning network 28'' and the frequency of oscillator 26A''. Furthermore, transmitter controller 22'' may make the adjustments already described above based on measurements by load detector 24A, shown in Figure 6, which more closely illustrates the circuits of transmitter modules 20 and 20''. Load detector 24A detects the effect of load 70'' at point 24E in Figure 6.The receiver controller 42'' may also adjust one or more of the settings of the receiver tuning network 48'' and the load management system 46E'' to improve the efficiency of power transmission based on measurements from the receiver power sensor 44A and the load detector 44B (both shown in Figure 7). Given the power adjustment function of system 10'', it will be understood that there is no prior reason that the power transmission function of the system should be limited to short-range wireless transmission across an air gap, as shown in Figure 19A. Therefore, in another embodiment, a power adjustment unit 410 is shown in Figure 19B based on the elements of system 10'' in Figure 19A. The transmitter tuning network 28'' communicates directly with the receiver tuning network 48'' via a suitable non-air-gap connection 60''. This communication is via high-frequency power signals, which constitute the transmission of power within and by the system. The DC voltage and DC current levels of the transmitter module 20'' may be isolated from such levels of the receiver module 40'' using electronic components of appropriate reactance in a known configuration. The transmitter resonator 30'' and receiver resonator 50'' are absent in this embodiment and are unnecessary due to the direct communication connection between the transmitter tuning network 28'' and the receiver tuning network 48''. The function of the power transmission system in Figures 19A and 19B as a power regulation system can be better understood by considering Figure 19B, in particular, that the concept of power regulation is simplified by the absence of the transmitter resonator 30'' and receiver resonator 50'', but these also apply equally to these resonators that are present (as in Figure 19A). The systems in Figures 19A and 19B have four independent control parameters that can be adjusted in operation to regulate the power transmitted to the receiver module 40'' and, consequently, to the load 70''. Typical commercial power regulation units are commonly known as "boost converters" because they raise the output voltage above the supply voltage. These devices have only two control parameters. A first independent control parameter that can be adjusted in operation to adjust the power transmitted to receiver module 40'' and, consequently, load 70'' is the oscillation frequency of power amplifier 26B'', which is adjustable by controller 22A'' in oscillator 26A''. A second independent control parameter that can be adjusted in operation to adjust the power transmitted to receiver module 40'' and, consequently, load 70'' is the output load of rectifier 46D of receiver module 40''. This output load consequently directly determines the input impedance of rectifier 46D and, consequently, receiver module 40''. This consequently is the load on transmitter module 20'' and directly determines the input DC equivalent resistance of power amplifier 26B''. The operation of the output load of rectifier 46D is performed via the load management system 46E'' of receiver module 40'' (see Figure 19A) under the control of receiver controller 42''. This second independent control parameter is a property of the receiver module but essentially controls the load on the power supply. The control point for manipulating this parameter is the load management system 46E'' of the receiver module 40''. A third and fourth independent control parameter, which can be adjusted in operation to regulate the power transmitted to the receiver module 40'' and, consequently, to the load 70'', are the properties of the rectifier 46D (see Figure 7) and the power amplifier 26B'' (Figure 19A) of the receiver module 40'', which are essentially similar but completely independent of each other. Both the rectifier 46D and the power amplifier 26B'' comprise multi-terminal amplification devices and rely on the modulation of the current flow between two terminals through the multi-terminal device by a voltage signal applied to a third terminal of each device. The simplest multi-terminal amplification device that can be used in each of the rectifier 46D and the power amplifier 26B'' is a transistor. This allows for a phase difference between the voltage signal and the current signal generated by or within the device. This voltage-current phase difference can be adjusted by the applied voltage. The rectifier 46D may be an adjustable phase high-frequency rectifier in which the voltage-current phase difference can be adjusted via the receiver controller 42''.In the case of power amplifier 26B'', the voltage-current phase difference may be adjusted via transmitter controller 22''. Rectifier 46D may effectively comprise a differential self-synchronous high-frequency rectifier. Rectifier 46D may, in particular, comprise a differential switch-mode self-synchronous high-frequency rectifier. The examples in Figures 19A and 19B are based on transmitting power from a solar cell, or by extension, a solar cell array, where the power supplied by solar cell 420 can vary significantly, down to zero, depending on sunlight. There are many other power sources whose output fluctuates, both in terms of power and the voltage produced. These include power generation turbines, wind turbines, and various batteries and condensates. Wind turbines can vary significantly in their power output, and the power depletion curves of various batteries can span a wide range. Given the efficiency of power transmission of the systems, either of these systems 10'' and 410 may be configured to receive power from commercially available batteries having, for example, but not limited to, slow open-circuit voltage decay curves. The load management system 46E'' may be configured to change the input DC equivalent resistance of the power amplifier 26B'', as already described above, and the controllers 22'' and 42'' may be configured to supply the required voltage level to the load 70'' until such a voltage can no longer be maintained by the transmitted power and the degree of adjustment of the parameters of systems 10'' and 410. Figure 19A and its accompanying explanatory text deal with the short-range wireless transmission of power from a single solar cell 420 to a single load 70'', which is typically a battery. In actual implementations of larger solar power systems, an array of batteries is typically used, and as a result, a power transmission scheme similar to that described with reference to Figures 12, 13A, and 13B can be used, with multiple transmitter subsystems and typically a single receiver subsystem. This situation is shown in Figures 20A and 20B, which are exploded front and rear views of a solar panel 400, respectively, and the solar panel 400 has a transparent solar cell cover 440 having one short-range wireless power transmission subsystem for each solar cell 420, thereby comprising, as an example, 60 short-range wireless power transmission subsystems 16, each transmission subsystem 16 comprising a transmitter resonator 30'', a transmitter module 20'', and a power regulating unit 430, as described with reference to Figure 19A. To avoid confusion, the transmission subsystem 16 is not labeled in Figure 19A, but is shown and labeled in Figures 20B, 21B, and 22B, as will be further explained below. In one embodiment, cell-level power management is enabled by coupling each individual solar cell of a solar panel, which consists of multiple solar cells, to a power transmission and management system. Providing power management at the individual cell level allows for optimization of power collection on a cell-by-cell basis, thereby improving the overall efficiency of the solar panel system. In such embodiments, the impact of individual cell failures or poor connections between cells is mitigated. Power collection at the individual cell level enables maximum power harvesting even under less-than-ideal conditions, such as when rain, shade, or debris covers part of the solar panel. To avoid complexity, only the short-range wireless power transmission subsystem 16 is labeled in Figure 20B. In Figures 20A and 20B, the transmitter resonator 30'' of each transmission subsystem 16 may be located on the back of its corresponding solar cell 420. In Figure 20A, the flat area of ​​the solar cell viewed from the front of the panel represents the active semiconductor device itself that receives solar radiation and converts energy, and is correspondingly labeled 420, while in Figure 20B, the flat area of ​​that device viewed from the back represents the transmitter resonator, and is correspondingly labeled 30''. The transmitter resonator 30'' may have a surface area that is at least a large portion of the range of the active solar radiation receiving surface of the solar cell 420. The transmitter module 20'' and power regulating unit 430 of each short-range wireless power transmission subsystem 16 are integrated together in Figure 20B and labeled 450. To avoid complexity, the integrated component 450 is not labeled in Figure 19A, but is shown and labeled as a unit in Figures 20B, 21B, and 22B, as will be further explained below. A single receiver resonator 50'' may be mounted on the frame 460 of the solar panel 400. A single receiver module 40'' may be mounted directly on the back of the receiver resonator 50''. During operation, the near-range resonant wireless power transmission system 10'' may function in the same way as the near-range resonant wireless power transmission system 10' in Figures 12, 13A, and 13B, but with all power amplifiers 26B'' having the applied voltage V DD This is replaced by a power signal from the power control unit (PCU) 430, which in turn receives its power from the associated solar cell 420. In another embodiment of the system shown in Figures 20A and 20B, the frame 460 may be configured to be a receiver resonator suitable for receiving power from all transmitter resonators 30'', and the receiver module 40'' may be located on the frame 460. In this embodiment, the plate in the frame may not be a resonator but a simple flat sheet of non-conductive material. In another implementation, the solar panels 400' shown in front and rear views in Figures 21A and 21B, respectively, transmit power from each near-field wireless power transmitting subsystem to one near-field wireless power receiving subsystem. Frame 460 is shown as being filled with an opaque plate 470, although plate 470 may not be part of the near-field electrical or magnetic circuit. For clarity, the transmitting side uses the same numbering as in Figures 20A and 20B. The receiving side uses the numbering in Figure 19A. Again, to avoid confusion, only one receiving device is labeled. During operation, the solar panel configuration 400' in Figures 21A and 21B may have individual transmitter modules 20'' linked by hardwires (not shown) so that they are in phase, thereby minimizing power loss during transmission. In other embodiments, the transmitter modules 20'' may be independent and function as described in Figures 14, 17, and 18. In yet another implementation, shown in Figures 22A and 22B as solar panel configuration 400'' in front and rear views, respectively, an array of, for example, 25 solar cells is shown, arranged in five rows of cells 420, with five cells in each row. Each solar cell 420 has a transmitter resonator 30'' at its rear, and a unit 450 comprising its corresponding transmitter module 20'' and power regulating unit 430. Receiver resonators 50'' are located at the bottom and top of the array and between each two rows of solar cells, positioned in a plane substantially perpendicular to the plane of the solar cells 420, and each receiver resonator 50'' communicates via wired telecommunications with its corresponding receiver module 40''. As with the previously described embodiments of the solar panel, an example of each component is labeled. As with the implementations shown in Figures 20A and 20B, and also in Figures 21A and 21B, the solar panel configuration 400'' may have a frame 460 in some embodiments. For clarity, the frame 460 is not shown in Figures 22A and 22B.

[0300] During operation, the transmitter resonators 30'' of the solar cells 420 in a particular row of the system 400'' transmit power to the receiver resonators 50'' both above and below them. However, in this embodiment, there is an additional mechanism in which various nearest neighbor receiver resonators 50'' are resonantly coupled and share the collected power among them. Thus, the collected power gathered by all the receiver resonators 50'' of the array may be taken out through any one or more of the various receiver modules 40''. In particular, the power gathered by all the receiver modules 40'' may be taken out, for example, only through the bottommost receiver module 40''. Any one of the receiver modules 40'' on any resonator 50'' can function as a receiver module that collects power from the row of solar cells 420, while also functioning as a transmitter module that transmits the collected power through its associated resonator 50'' to another nearby resonator 50''. This operation may be repeated downwards in the array to transmit power to the bottommost receiver module 40''.

[0301] In another embodiment of the system in Figures 22A and 22B, a frame similar to the frame 460 in Figures 20A and 20B, surrounding the plane of the solar cell array in Figures 22A and 22B, may be a receiver resonator supporting a receiver module 40'' and may receive power from various resonators 50''. In this way, the total power generated by all solar cells 420 in the array may be received by the resonator frame 460 and taken out for further electrical transmission via the receiver module 40''.

[0302] Power collection at the individual solar cell level can be achieved via wired connections. However, using a wireless transmission system for solar panels can reduce wiring and thus lower manufacturing costs.

[0303] A further embodiment, as illustrated with reference to the flowchart in Figure 23, provides a method for transmitting power from a photocell 420 to a power load 70''

[1500] , the method comprising: in a transmitting module 20'', converting power from the photocell 420 into an oscillating power signal having an oscillating frequency

[1510] ; transmitting power to a transmitter resonator 30'' configured to resonate with the transmitting module 20'' via wired telecommunications and to resonate at the oscillating frequency

[1520] ; receiving power in a receiver resonator 50'' configured to resonate at the oscillating frequency and arranged to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction

[1530] ; receiving power in a receiver module 40'' configured to resonate with the receiver resonator 50'' via wired telecommunications

[1540] ; and providing the received power in DC form to a power load 70'' via wired telecommunications

[1550] . This method may further include converting the voltage and current of the power from the photocell 420 to voltages and currents that are compatible with the transmitting module 20'' before converting the power into an oscillating power signal.

[0304] A further embodiment of the method described with reference to the flowcharts in Figures 19A and 24, is a method for transmitting power from an array of photocells 420 to a power load 70''

[1600] , wherein each of a first plurality of corresponding transmitting modules 20'' converts power from each of the photocells 420 in the array 400 into an oscillating power signal having an oscillating frequency

[1610] , and each of the transmitting modules 20'' corresponds to a second plurality of transmitter resonators 30'', each configured to resonate at the oscillating frequency. A method is provided which includes transmitting power to a resonator 30''

[1620] , receiving power in a receiver resonator 50'' configured to resonate at an oscillation frequency and arranged to receive power from a plurality of transmitter resonators 30'' via at least one of capacitive coupling and magnetic induction

[1630] , receiving power in a receiver module 40'' which is in wired telecommunications with the receiver resonator 50''

[1640] , and providing the received power in DC form via wired telecommunications to a power load 70''

[1650] . The method may further include converting the voltage and current of the power from each photocell 420 to voltage and current suitable for the corresponding transmitter module 20'' before converting the power into an oscillation power signal. Receiving power in the receiver resonator 50''

[1630] may include receiving power in receiver resonators arranged around the plane of the array of photocells 400.

[0305] In a further embodiment of the method described with reference to the flowcharts in Figures 19A and 25, a method for transmitting power from an array of photocells 420 400' to a power load 70''

[1700] is provided, in each of a first plurality of corresponding transmitting modules 20'', to convert power from each of the photocells 420 in the array 400' into an oscillating power signal having an oscillating frequency

[1710] , and to transmit power from each of the transmitting modules 20'' to a corresponding transmitter resonator 30'' of a second plurality of transmitter resonators 30'', each transmitter resonator 30'' being configured to resonate at the oscillating frequency [17 A method is provided which includes receiving power from each transmitter resonator 30'' in a corresponding receiver resonator 50'' configured to resonate at the oscillation frequency, wherein each receiver resonator 50'' is further configured and arranged to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction

[1730] , receiving power from each receiver resonator 50'' in a corresponding receiver module 40'' which is in wired telecommunications with the receiver resonator 50''

[1740] , and providing the received power in DC form via wired telecommunications to a power load 70''

[1750] . The method may further include converting the voltage and current of the power from each photovoltaic cell 420 to voltage and current suitable for the corresponding transmitter module 20'' before converting the power to an oscillating power signal.

[0306] In a further embodiment described with reference to the flowcharts in Figures 19A and 26, a method for transmitting power from an array of photocells 420 to a power load 70'' (Figure 19A)

[1800] is provided, in each of a first plurality of corresponding transmitting modules 20'', to convert power from each of the photocells 420 in the array 400'' into an oscillating power signal having an oscillating frequency

[1810] , and to transmit power from each of the transmitting modules 20'' to a transmitter resonator 30'' of a second plurality of transmitter resonators 30'', each transmitter resonator 30'' configured to resonate at the oscillating frequency

[1820] , and configured to resonate at the oscillating frequency A method is provided which includes receiving power from each transmitter resonator 30'' in any adjacent receiver resonator 50'' of a third plurality of receiver resonators 50'', wherein each receiver resonator 50'' is further configured and arranged to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction

[1830] , sharing the received power among the third plurality of receiver resonators 50''

[1840] , and providing the received power from one or more of the third plurality of receiver resonators 50'' in DC form via wired telecommunications to a power load 70'' via one or more corresponding receiver modules 40''

[1850] . The method may further include converting the voltage and current of the power from each photovoltaic cell 420 to voltage and current suitable for the corresponding transmitter module 20'' before converting the power into an oscillating power signal.

[0307] Figure 27A shows a typical portion 500 of an extended short-range wireless power distribution system in an electric vehicle having a conductive chassis 510. In this embodiment of the overall system 10'' in Figure 19A, the power source is a rechargeable battery 520 instead of a solar cell 420, and the load 70'' is an electric motor 530 instead of the battery in Figure 19A. The system shown in Figure 14A may optionally include a power adjustment unit 430 as in Figure 19A. In other embodiments, the transmitter modules may function together to provide power adjustment, as described above with reference to Figure 19B.

[0308] The system shown in Figure 27A and described in more detail below may operate by capacitive power transmission, inductive power transmission, or bimodal power transmission. Referring to Figures 4B and 19A, the transmitter resonator 30'' comprises a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to Figures 4B and 19A, the receiver resonator 50'' comprises a dielectric element 158 ​​sandwiched between conductive antennas 152 and 154. The transmitter module 20'' is shown mounted directly to antenna 132, which also functions as a frame or holder for battery 520. The transmitter module 20'' may be electrically connected between battery 520 and transmitter resonator 30''. The receiver module 40'' is shown mounted directly to electric motor 530. The receiver module 40'' may be electrically connected between receiver resonator 50'' and motor 530.

[0309] Figure 27B shows a typical portion 500' of an extended short-range wireless power distribution system in an electric vehicle having a conductive chassis 510. In this embodiment of the overall system 10'' in Figure 19A, the power source is, again, as in Figure 27A, a rechargeable battery 520 instead of a solar cell 420, and the load 70'' is an electric motor 530 instead of a battery in Figure 19A. The system shown in Figure 27B may optionally include a power adjustment unit 430 as in Figure 19A. In other embodiments, the transmitter module 20'' and the receiver module 40'' may function together to provide power adjustment, as described above with reference to Figure 19B.

[0310] The system shown in Figure 27B and described in more detail below can operate by capacitive power transmission, inductive power transmission, or bimodal power transmission. Referring to Figures 4B and 19A, the transmitter resonator 30'' comprises a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to Figures 4B and 19A, the receiver resonator 50'''' includes a dielectric element 158 ​​and a conductive antenna 152, the antenna 154 in Figure 27A being absent in the resonator 50'' in this embodiment. The transmitter module 20'' is shown mounted directly to the antenna 132, which also functions as a frame or holder for the battery 520. The transmitter module 20'' may be electrically connected between the battery 520 and the transmitter resonator 30''. The receiver module 40'' is shown mounted directly to the electric motor 530. In this embodiment, the receiver module 40'' may be electrically connected between the motor 530 and the chassis 510. In this configuration, there is sufficient coupling between the chassis 510 and the antenna 152 for power transmission with adequately high efficiency. Conductive mechanical components of the system, i.e., components having load-bearing structural functions within the system, may form part of the resonant structure of the power transmission system.

[0311] The embodiments shown in Figures 27A and 27B focus particularly on the power supplied to an electric motor 530 that drives one of the vehicle's wheels, but an equivalent configuration may be implemented for any electrical subsystem of the vehicle using a plurality of appropriately fitted receiver modules 40'', all of which are powered by a transmitter module 20''.

[0312] The configurations in Figures 27A and 27B for power transmission from the battery to the vehicle's electrical subsystems eliminate the need for the highly complex automotive wire harnesses that cause difficulties during vehicle manufacturing and result in significant manufacturing costs. The embodiments in Figures 27A and 27B, along with their extension to other electrical subsystems of the vehicle, can be described as an "extended short-range wireless power distribution system."

[0313] In addition to the wheels of an electric vehicle, this configuration may extend to headlights and other vehicle accessories, including, but not limited to, interior lights, dashboard displays, gauges, digital electronics, navigation systems, and warning systems. Furthermore, the application is not limited to electric vehicles. It may be applied to hybrid vehicles and internal combustion engine vehicles, with power distribution as needed. It may also be applied to any other vehicle employing an electrical system that requires power. Examples include, but not limited to, electric and non-electric bicycles, aircraft, boats, and other vehicles that use onboard power sources. The battery or power source does not have to be mounted on the vehicle. The principles described with respect to Figures 1-11, 19A-19B, and 27A-27B also apply to stationary and vehicle systems that require power to be supplied from a stationary power source, such as, but not limited to, fixed rails for providing power to a moving vehicle.

[0314] Figure 28A shows another embodiment of the overall system 10'' of Figure 19A in a power supply system 600 for supplying power to a computer monitor 610 placed on a desk tabletop 620 from a suitable power source via a primary side 12 shown in Figure 1, and more specifically in Figure 6. In system 600, both the transmitter module 20'' and the transmitter resonator 30'' of Figure 19A are incorporated into the primary side 12. In the configuration of system 600, the receiver resonator 50'' shown in Figure 19A forms the base of the monitor 610. The receiver module 40'' of Figure 19A may be incorporated into the base of the monitor 610. Alternatively, the receiver module 40'' of Figure 19A may be incorporated inside the monitor 610 itself. Referring to Figure 4B, the antenna 152 forms the bottom of the base of the monitor 610 and is isolated from the antenna 154 by a dielectric 158.

[0315] The housing and structural frame 630 of the monitor 610 may be at least partially conductive and act as one adjacent conductor that electrically supplies power signals from the antenna 154 to the circuit of the monitor 610 representing the load resonator 70'' in Figure 19A via the receiver module 40'' (see Figure 19A). Another electrical connector from the antenna 152 to the circuit of the monitor 610 extends from the antenna 152 to the pedestal of the monitor 610. In other embodiments, the housing and structural frame 630 of the monitor 610 may be made of a non-conductive polymer, with a separate conductor extending from the antenna 154 to the circuit of the monitor 610 representing the load resonator 70'' in Figure 19A.

[0316] As shown in another embodiment of the power supply system 600' for supplying power to the computer monitor 610 in Figure 28B, the base of the monitor 610 may comprise only the antenna 152 and the dielectric 158. In this embodiment, a metallic conductive portion of the monitor housing or frame 630 functions as an antenna instead of the antenna 154, and the housing or frame 630 is well coupled with the antenna 152 under the dielectric 158 to provide adequately efficient power transmission. The receiver module 40'' in Figure 19A may be incorporated into the base of the monitor 610. Alternatively, the receiver module 40'' in Figure 19A may be incorporated inside the monitor 610 itself. The housing and structural frame 630 of the monitor 610 may function as one adjacent conductor supplying power signals to the circuit of the monitor 610 representing the load resonator 70'' in Figure 19A via the receiver module 40''.

[0317] The system 600 may optionally include a power adjustment unit 430, as shown in Figure 19A. In some embodiments, the transmitter module 20'' and the receiver module 40'' use short-range wireless power transmission, as described with reference to Figure 19A, but may also function together to provide power adjustment. The short-range wireless power transmission system in Figure 28A eliminates the need for cumbersome power cables to supply power to the monitor 610, using the system's mechanical structural elements as integrated electrical / electronic components in the power transmission configuration.

[0318] As described with reference to the flowchart in Figure 29 and the systems in Figures 19A and 19B, a method for transmitting power from a DC power supply 420 to a power load 70'' is provided, comprising a power transmission system 10'', 410 that communicates with the power supply 420 via wired telecommunications, wherein the power transmission system 10'', 410 comprises an oscillator 26A'' capable of oscillating at an oscillation frequency, a power amplifier 26B'' and a transmitter tuning network 28'' both under the control of a transmitter controller 22'', a receiver tuning network 48'' and a load management system 46E'' both under the control of a receiver controller 42'', and the load management system 46E'' communicates with the power load 70'' via wired telecommunications, comprising the receiver tuning network 48'' and load management system 46E''. A method is further provided which includes

[2010] converting power from a power supply 420 into an oscillating power signal having an oscillating frequency in a power amplifier 26B''

[2020] , transmitting the power signal from the power amplifier 26B'' to a load management system 46E'' via a transmitter tuning network 28'' and a receiver tuning network 48'' under the control of a transmitter controller 22''

[2030] , changing the power transmission rate by adjusting at least one of the oscillating frequency, the input DC equivalent resistance of the power amplifier 26B'', the transmitter tuning network 28'', the receiver tuning network 48'', and the load management system 46E''

[2040] , and providing the power received by the load management system 46E'' to a power load 70'' in the form of DC via wired telecommunications

[2050] .

[0319] Transmitting power signals via the transmitter tuning network 28'' and the receiver tuning network 48''

[2030] may include transmitting power by wired or wireless communication. Transmitting power by wireless communication may include transmitting power by short-range wireless communication. Transmitting power by short-range wireless communication may include transmitting power by at least one of capacitive coupling and inductive coupling. Transmitting power from the DC power supply 420 may include transmitting power from at least one solar cell 420. Transmitting power from the DC power supply may include transmitting power from at least one battery. Transmitting power from the DC power supply may include transmitting power from power supplies of various voltages.

[0320] In another embodiment, which will be described with reference to the flowchart in Figure 30 and will examine the systems in Figures 19A and 19B in more detail, a method is provided for transmitting power from a DC power supply 420 to a power load 70''

[2100] , which provides a power transmission system 10'', 410 that wired telecommunicates with the power supply 420, wherein the power transmission system 10'', 410 comprises a high-frequency power amplifier 26B'' that high-frequency communicates with an adjustable phase high-frequency rectifier 46D (see Figure 7) that is wired electrical contact with the power load 70''

[2110] , and the method is provided which includes, in the amplifier 26B'', converting power from the DC power supply 420 into a high-frequency oscillating power signal

[2120] , in the rectifier 46D, converting the high-frequency oscillating power signal into a DC power signal

[2130] , and adjusting the efficiency of power transmission by adjusting the current-voltage phase characteristics of the rectifier 46D

[2140] . Providing an adjustable phase high-frequency rectifier may include providing a differential self-synchronizing high-frequency rectifier 46D.

[0321] Method

[2100] may further include adjusting the efficiency of power transmission by adjusting the DC equivalent input resistance of amplifier 26B''. Providing power transmission systems 10'', 410

[2110] may also include providing a load management system 46E'' that wire-communicates between a rectifier 46D and a load 70''. Adjusting the DC equivalent input resistance of amplifier 26B'' may include adjusting the input impedance of rectifier 46D by adjusting the load management system 46E''. Adjusting the load management system 46E'' may include automatically adjusting the load management system 46E''.

[0322] Method

[2100] may further include adjusting the efficiency of power transmission by adjusting the current-voltage phase characteristics of the power amplifier 26B''. Providing the power transmission system 10'', 410

[2110] may include providing a transmitter controller 22'' that communicates with the power amplifier 26B'' to control the power amplifier 26B''. Adjusting the current-voltage phase characteristics of the power amplifier 26B'' may be performed by the transmitter controller 22''. Adjusting the current-voltage phase characteristics of the power amplifier 26B'' may be performed automatically by the transmitter controller 22''.

[0323] Method

[2100] may further include adjusting the efficiency of power transmission by changing the oscillation frequency of the power amplifier 26B''.

[0324] Providing a power transmission system 10'', 410

[2110] may include providing a receiver controller 42'', which communicates with the rectifier 46D to control the rectifier 46D. Adjusting the current-voltage phase characteristics of the rectifier 46D may be performed by the receiver controller 42'', or it may be performed automatically by the receiver controller 42'', which communicates with the rectifier 46D to control the rectifier 46D.

[0325] Providing a power transmission system 10'', 410

[2110] may include providing a power amplifier 26B'', which communicates directly via wired high frequency with an adjustable phase high frequency rectifier 46D (via connection 60'', in Figure 19B). Providing a power transmission system 10'', 410

[2110] may also include providing a power amplifier 26B'', which communicates wirelessly short-range high frequency with an adjustable phase high frequency rectifier 46D.

[0326] Providing a power transmission system 10'', 410

[2110] may include providing a transmitter resonator 30'', which communicates with a power amplifier 26B'', and a receiver resonator 50'', which communicates with a high-frequency rectifier 46D. Method

[2100] may further include operating the transmitter resonator 30'', and the receiver resonator 50'', with respect to each other in wireless short-range high-frequency communication. Providing a power transmission system 10'', 410

[2110] may also include providing a power amplifier 26B'', which communicates with the rectifier 46D in at least one of capacitive short-range wireless high-frequency communication and inductive short-range wireless high-frequency communication. Providing a power transmission system 10'', 410

[2110] may also include providing a power amplifier 26B'', which communicates with the rectifier 46D in bimodal wireless short-range communication.

[0327] Method

[2100] may further include providing a power adjustment unit 430 electrically positioned between a power supply 420 and a power transmission system 10'', and adjusting the power adjustment unit 430 to adjust at least one of the current and voltage from the power supply 420 to improve the efficiency of power transmission.

[0328] Referring to Figure 7, based on a more detailed examination of the systems in Figures 19A and 19B, the power transmission system 10'', 410 for supplying power from a DC power supply 420 to a power load 70'' comprises: a high-frequency power amplifier 26B'' configured to communicate with the power supply 420 via wired electrical communication and to convert the DC voltage from the power supply 420 into an AC voltage signal having an oscillating frequency; an adjustable phase high-frequency rectifier configured to receive power transmitted from the power amplifier 26B'' and to communicate with the power amplifier via high-frequency communication with the power load 70''; and a receiver controller 42'' configured to communicate with the rectifier 46D and to adjust the efficiency of power transmission from the power amplifier 26B'' to the rectifier 46D by adjusting the current-voltage phase characteristics of the rectifier 46D. The receiver controller 42'' may be configured to automatically adjust the current-voltage phase characteristics of the rectifier 46D. The rectifier may be a differential self-synchronizing high-frequency rectifier.

[0329] The power transmission systems 10'' and 410 may further include a load management system 46E'' which is power-signally positioned between the load 70'' and the rectifier 46D and communicates with the load 70'' via a wire, and the load management system 46E'' is configured to improve the efficiency of power transmission by adjusting the input impedance of the rectifier 46D. The load management system 46E'' may be configured to automatically adjust the input impedance of the rectifier 46D.

[0330] The power transmission systems 10'', 410 may further include a transmitter controller 22'', which communicates with the amplifier 26B'', and the transmitter controller 22'', is configured to improve the efficiency of power transmission by adjusting the current-voltage phase characteristics of the amplifier 26B'', or the transmitter controller 22'', which may be configured to automatically adjust the current-voltage phase characteristics of the amplifier 26B'', thereby improving the efficiency of power transmission.

[0331] The power transmission systems 10'' and 410 may further include an oscillator 26A'' that communicates with an amplifier 26B'' and a transmitter controller 22''. The transmitter controller 22'' may be configured to adjust the oscillation frequency via the oscillator 26A''.

[0332] The power amplifier 26B'' may communicate directly via wired high-frequency communication with the adjustable phase high-frequency rectifier 46D (via connection 60'' in Figure 19B). The power amplifier 26B'' may communicate wirelessly via short-range high-frequency communication with the adjustable phase high-frequency rectifier 46D. The power transmission systems 10'', 410 may include a transmitter resonator 30'' that communicates via wired high-frequency communication with the power amplifier 26B'' and a receiver resonator 50'' that communicates via wired high-frequency communication with the rectifier 46D. The transmitter resonator 30'' and the receiver resonator 50'' may communicate wirelessly via short-range high-frequency communication with each other. The power amplifier 26B'' may perform at least one of capacitive short-range wireless high-frequency communication and inductive short-range wireless high-frequency communication with the rectifier 46D. The power amplifier 26B'' may communicate bimodal short-range wireless high-frequency communication with the rectifier 46D.

[0333] The power transmission system may further include a power adjustment unit 430 electrically positioned between the power supply 420 and the power amplifier 26B'', the power adjustment unit 430 being configured to adjust at least one of the current and voltage from the power supply 420 to improve the efficiency of power transmission.

[0334] In another embodiment described with reference to Figures 19A, 19B, 27A and 27B, and 28A and 28B, the electric system comprises a mechanical load-bearing structure 510, 630 having a conductive first portion, and a power transmission system 10'', 410 comprising a power load and at least one high-frequency resonator 30'', 50'', configured for short-range wireless power transmission, wherein the resonator has at least a partially conductive first portion. The electric system may further comprise a rechargeable battery 520, and the power load may comprise an electric motor 530. The electric system may also comprise an electric vehicle 500, 500'', and the mechanical load-bearing structure may include the vehicle chassis 510. The electric system may also comprise a display monitor 610, and the mechanical load-bearing structure may be at least one of the monitor frame 630 and base.

[0335] The electric system may further include a power supply. The power transmission system may include a high-frequency power amplifier 26B'' configured to communicate with a power supply via wired electrical communication and to convert a DC voltage from the power supply into an AC voltage signal having an oscillating frequency; an adjustable phase high-frequency rectifier 46D, which is in wired electrical contact with a power load 70'' and communicates with the power amplifier 26B'' via high frequency, and is configured to receive power transmitted from the amplifier 26B''; and a receiver controller 42'' communicating with the rectifier 46D, which is configured to adjust the efficiency of power transmission from the amplifier 26B'' to the rectifier 46D by adjusting the current-voltage phase characteristics of the rectifier 46D.

[0336] In another embodiment, as shown in Figures 19A and 19B, 27A and 27B, and 28A and 28B, the apparatus comprises mechanical load-bearing structures 510, 630 having conductive first parts; a power supply; power loads 70'', 530, 610; a power transmission system comprising a high-frequency power amplifier 26B'', configured to wire-communicate with the power supply and convert a DC voltage from the power supply into an AC voltage signal having an oscillating frequency; and an adjustable phase high-frequency rectifier 46D, which is in wire-communicate with the power load 70'', and to high-frequency communicate with the power amplifier 26B'', The power transmission systems 10'', 410, each comprising an adjustable phase high-frequency rectifier 46D configured to receive power transmitted from amplifier 26B'', and a receiver controller 42'', communicating with the rectifier 46D and configured to adjust the efficiency of power transmission from amplifier 26B'', to the rectifier 46D by adjusting the current-voltage phase characteristics of the rectifier 46D, wherein the conductive first portion is arranged to carry at least one high-frequency signal from amplifier 26B'', to the rectifier 46D.

[0337] The device may further include a load management system 46E'' which is power-signal-oriented between the load 70'' and the rectifier 46D and communicates with the load 70'' via a wire, and the load management system 46E'' is configured to improve the efficiency of power transmission by adjusting the input impedance of the rectifier 46D. The device may further include a transmitter controller 22' which communicates with the amplifier 26B'', and the transmitter controller 22' is configured to improve the efficiency of power transmission by adjusting the current-voltage phase characteristics of the amplifier 26B''. The device may further include an oscillator 26A'' which communicates with the amplifier 26B'' and the transmitter controller 22', and the transmitter controller 22' is configured to adjust the oscillation frequency via the oscillator 26A''.

[0338] The power amplifier 26B'' may communicate directly with the rectifier 46D via a wired high-frequency communication via a conductive first portion. The power amplifier 26B'' may communicate with the rectifier 46D wirelessly via short-range high-frequency communication. The power transmission systems 10'', 410 may include a transmitter resonator 30'' that communicates with the power amplifier 26B'' via a wired high-frequency communication and a receiver resonator 50'' that communicates with the rectifier 46D via a wired high-frequency communication, and one of the transmitter resonator 30'' and the receiver resonator 50'' may include a conductive first portion. The transmitter resonator 30'' and the receiver resonator 50'' may communicate with each other wirelessly via short-range high-frequency communication. The power amplifier 26B'' may perform at least one of capacitive short-range wireless high-frequency communication and inductive short-range wireless high-frequency communication with the rectifier 46D. The power amplifier 26B'' may communicate with the rectifier 46D bimodal short-range wireless high-frequency communication. The DC power supply may include a rechargeable battery 520, and the load may include an electric motor 530.

[0339] Further embodiments schematically shown in Figure 32 and based on Figures 6, 7, 8, and 9 include a sealed bidirectional power transmission circuit device 800 comprising a plurality of terminals arranged for electrical communication with an external device of the sealed device 800, wherein the sealed device 800 comprises a multi-terminal power switching (MPS) device 810 having at least one DC terminal, at least one AC terminal, and at least one control terminal within its sealing, which is adjustable between an amplified state and a rectified state, and which communicates DC voltage and DC current bidirectionally via at least one DC terminal, and high-frequency power having amplitude, frequency, and phase via at least one AC terminal. A sealed bidirectional power transmission circuit device 800 is provided, comprising an MPS device 810 configured to communicate signals bidirectionally, and a phase, frequency, and duty cycle adjustment (PFDCA) circuit 820 that communicates wired data with a controller 880 and wired electrical with the MPS device 810 via at least one control terminal, wherein the PFDCA circuit 820 is configured to adjust the MPS device 810 between an amplified state and a rectified state by establishing a high-frequency oscillation signal having the frequency and phase of a high-frequency power signal at at least one control terminal of the MPS device 810 and adjusting the phase of the high-frequency oscillation signal under command from the controller 880. The PFDCA circuit 820 may be further configured to establish the duty cycle of the high-frequency oscillation signal. The PFDCA circuit 820 may include a high-frequency oscillator for generating the high-frequency oscillation signal under command from the controller 880. The term "multi-terminal power switching device" is used herein to describe a device having at least three terminals and capable of switching or modulating the current flowing between at least two of the terminals based on a signal applied to at least a third terminal of the device.Suitable MPS devices 810 include, but are not limited to, mechanical relay switches, solid-state switches, electro-optic switches (also called optoswitches, thyristors, and waveguide switches), transistors (including, for example, MOSFETs, MESFETs, III-V semiconductor transistor devices, and BJT devices), and power amplifier tube devices, including, for example, triodes and pentodes.

[0340] In some embodiments, the circuit is sealed with a polymer coating or polymer mold to create a sealed or sealed device. In some embodiments, the sealed device protects components located inside the device. In some embodiments, the sealing of the device provides electrical insulation to prevent electrostatic discharge, short circuits, or other harmful discharges that could damage the device's components. In some embodiments, sealing the device protects against oxidation of internal components. In some embodiments, the sealing may create a waterproof barrier or a water vapor barrier. In some embodiments, the sealing facilitates electrical connection to the device by providing access to one or more terminals located outside the sealed device.

[0341] The sealed power transmission circuit device 800 may further include a tuning network 830 within the encapsulation that communicates with a controller 880 via wired data communication and with an MPS device 810 via wired electrical communication through at least one AC terminal, wherein the tuning network 830 is configured to adjust the high-frequency power signal to a tuned high-frequency power signal from the tuning network 830 when the MPS device 810 is in an amplified state, under command from the controller 880. The tuning network 830 may include a harmonic termination network circuit of the type shown in Figures 8 and 9, configured to suppress harmonics of the high-frequency oscillation signal in the high-frequency power signal. As shown in Figures 8 and 9, the harmonic termination network may include one or more inductors and one or more of the following: first harmonic terminations 127I, 147G, second harmonic terminations 127H, 147F, and third harmonic terminations 127F, 147D.

[0342] The sealed power transmission circuit device 800 may include an amplitude / frequency / phase detector (AFPD) 840 located within the encapsulation, which communicates with the controller 880 via wired data and with the tuning network via wired electrical communication, and which is configured to determine the amplitude, frequency, and phase of any high-frequency power signal communicated between the tuning network and an external AC load / source of the sealed device. For this purpose, the AFPD 840 measures the amplitude, frequency, and phase of the signal at the output of the tuning network 830 derived from the device 800, as shown in Figure 32. The PFDCA circuit 820 is configured to receive commands from the controller 880 based on the measurement data communicated to the controller 880 by the AFPD 840. In other embodiments, not shown in Figure 32, the PFDCA circuit 820 is configured to adjust a high-frequency oscillation signal and / or at least one of a DC current and a DC voltage based on a feedback signal received directly from the AFPD 840.

[0343] The tuning network 830 may include a voltage-current tuner to adjust the phase difference between the voltage and current of the tuned high-frequency signal based on measurement data from the AFPD 840 when the power switching device is in an amplified state. A suitable voltage-current tuner will be described in detail with reference to Figure 6. The voltage-current tuner of the tuning network 830 is applied to the signal directed to the signal connection derived from device 800, as shown in Figure 32. This allows it to function as a tuner when power is transmitted downward in Figure 32. The voltage-current tuner may also be transparent to power transmitted in the opposite upward direction through device 800 in Figure 32, and the power transmission circuit device 800 is bidirectional. In some implementations, the tuning network 830 may communicate the tuned high-frequency power signal with an AC load / source 900, which may be transmitter resonators 30 and 30'', as described with reference to Figure 6 and Figures 19A, 27A, and 27B. If the AC load / source 900 is such a bimodal transmitter resonator, the voltage-current tuner may function to adjust the ratio of the electric and magnetic fields, as described with respect to Figure 6.

[0344] The sealed power transmission circuit device 800 may further include a power management (PM) circuit 860 configured within the encapsulation to communicate via wired data with the controller 880 and via wired electrical communication between the MPS 810 and the external DC power supply / load 700 to match the impedance of the MPS 810 and the external DC power supply / load 700, and to adjust the DC power communicated between the MPS 810 and the DC power supply / load 700 based on measurement data communicated to the controller by the AFPD 840. In other embodiments, not shown in Figure 32, the PM circuit 860 may be configured to adjust the DC power communicated between the MPS 810 and the DC power supply / load 700 based on feedback signals received directly from the AFPD 840 and / or VID 850.

[0345] It should be noted again that DC power can be transmitted bidirectionally between the MPS810 and the DC power supply / load 700 via the PM circuit 860. Also, it should be noted that we maintain the convention of referring to the DC power supply / load 700 as "source / load" and the external AC load / source 900 that communicates AC power with the tuning network as "load / source," thereby emphasizing that when the DC power supply / load 700 functions as a source of DC power, the AC load / source 900 functions as a load of power converted to AC power, and vice versa. The arrows shown adjacent to and parallel to the connector in Figure 32 indicate the path and direction of power flow through device 800 when the MPS810 is in either its amplification or rectification state. When the MPS810 is in the amplification state, the power flow is downward in Figure 32, and when the MPS810 is in the rectification state, the power flow is upward in Figure 32.

[0346] The sealed power transmission circuit device 800 may further include a voltage / current detector (VID) 850 located within the encapsulation, which communicates via wired data with a controller 880 to determine the DC voltage and DC current passing between the MPS 810 and the PM circuit 860. When the MPS 810 is in the amplified state, the power transmission circuit device 800 may be adjusted based on the VID 850's readings so that the device 800 presents an equivalent DC load to the DC source / load 700 that allows for maximum power extraction from the DC source / load 700. This adjusts the DC voltage at at least one DC terminal of the MPS device 810. When the MPS 810 is in the rectified state, the power transmission circuit device 800 may be adjusted based on the VID 850's readings so that the device 800 presents an equivalent DC source impedance to the DC source / load 700 that allows for maximum power transmission from the device 800 to the DC source / load 700. This adjusts the DC voltage in the wired connection between device 800 and DC source / load 700.

[0347] The sealed power transmission circuit device 800 may further include a memory 870 within the encapsulation that communicates via wired data with the controller 880, AFPD 840, and VID 850, the memory 870 being configured to receive and store signal data from the two detectors 840 and 850, and to provide the signal data from the two detectors 840 and 850 to the controller 880. The memory 870 may be capable of storing the complete state of the device 800 for a series of consecutive instantaneous periods of time.

[0348] The tuning network may further comprise one or more of the following: a compensation network, a matching network, and a filter. The compensation network 26E, matching network 26D, and filter 26C in Figure 6 are suitable for this purpose, and the options are not limited to the devices in Figure 6.

[0349] The sealed power transmission circuit device 800 may include a controller 880 inside the encapsulation. In other embodiments, the sealed power transmission circuit device 800 may use an external controller equipped with appropriate input / output facilities for communicating data with various circuits incorporated inside the encapsulation of the device 800, and the controller may be programmed with appropriate software or firmware to perform all of the control procedures described above.

[0350] The sealed power transmission circuit device 800 may further include at least one communication circuit 890 that operates with one or more of the following technologies: Bluetooth, WiFi, Zigbee, and cellular technology, for bidirectional communication of information between the controller 880 and devices outside the sealed power transmission circuit device 800. The at least one communication circuit 890 may communicate bidirectionally with one or more suitable antennas 894. One or more antennas 894 may be located inside the encapsulation of the device 800, but it is generally more useful to have them located outside the device 800. One or more of the external devices may be other power transmission circuit devices, for example, other devices 800, and one or more other devices may form part of the collected power transmission system in other embodiments, for example, as described above in Figure 1.

[0351] The PFDCA circuit may be configured to adjust the duty cycle of the high-frequency oscillation signal based on measurements from the AFPD 840 and VID 850. In some embodiments, information regarding the measurements is transmitted to the controller 880, from there to the PFDCA circuit 820, where the duty cycle of the high-frequency oscillation signal is adjusted based on the received information. In other embodiments, although not shown in Figure 32, a feedback signal may be passed directly from the AFPD 840 and VID 850 to the PFDCA circuit 820, where the duty cycle of the high-frequency oscillation signal is adjusted based on the received feedback signal. By changing the duty cycle of the high-frequency oscillation signal, the PFDCA circuit 820 can adjust the direction of power flow through the device 800. If power is flowing from a DC source / load 700 through the device 800 to an AC load / source 900, the PFDCA circuit 820 can thereby adjust the DC power supplied to the device 800 by the source / load 700 and the AC power supplied from the device 800 to the AC load / source 900. When power is flowing from the AC load / source 900 through the device 800 to the DC source / load 700, the PFDCA circuit 820 can thereby adjust the AC power supplied to the device 800 by the AC load / source 900 and the power supplied to the DC source / load 700 by the device 800.

[0352] The controller 880 may communicate bidirectionally via a wired connection with an external device and circuit 898 (labeled "Ext." in Figure 32) located outside the encapsulation of device 800. This wired communication may be used, for example, to exchange data or to supply the controller 880 with a system clock synchronization signal for a system in which device 800 may be incorporated.

[0353] Referring to Figures 6 and 7, the sensors and detectors 24A, 24B, 24C, and 24D may be usefully positioned outside the encapsulation of the device 800.

[0354] The bidirectional power transmission circuit device 800 may also be effectively used to transmit and / or receive information through the power channel via the device 800 by mechanisms already described with reference to Figures 6 and 7. The power channel physically extends from the wired connection between the DC source / load 700 and the PM circuit 860 to the AC load / source 900 through the PM circuit 860, VID 850, MPS device 810, and tuning network 830. Along that physical power channel, the PM circuit 860, MPS device 810, and tuning network 830 are all under the control of the controller 880, which controls the MPS device 810 via the PFDCA circuit 820. The controller can modulate high-frequency power signals in the tuning network 830 and / or the MPS device 810 itself. The controller may also be configured to induce modulation of the DC voltage between the PM circuit 860 and the DC source / load 700. This makes it possible to modulate the information to a high-frequency power signal, a tuned high-frequency power signal, and / or the aforementioned DC voltage, and thereby communicate it to other devices outside of device 800. Such other devices may include further bidirectional power transmission circuit devices 800. The information may be modulated in digital or analog form to a high-frequency power signal, a tuned high-frequency power signal, and / or the aforementioned DC voltage. In other embodiments, the information may be modulated to a frequency different from the power transmission frequency. In other embodiments, the information may be modulated to harmonics of the power signal frequency. In yet another embodiment, the frequency of the high-frequency power signal may be a harmonic of the frequency of the signal to which the information is modulated. The above description has already explained how subsystems of the tuning network 830 can be used as suitable modulators.

[0355] Having described above how device 800 can be reconfigured between transmitter mode and rectifier mode operation, and how the power channel can be modulated, it is clear that device 800 can function as a full-duplex transceiver system for transmitting information in both directions. When two devices 800 are used in modules 20 and 40 in Figure 1, system 10 in Figure 1 may have additional secondary sides similar to the secondary side 14 in Figure 1. If additional secondary sides 14 are present, the above configuration allows for communication of information between the various secondary sides 14 and therefore with the primary side 12. The same full-duplex transceiver configuration is possible between transmitter module 20'' and receiver module 40'' used in the systems of Figures 19A and 19B using device 800 in Figure 32. The same applies to the systems shown in Figures 20A-22B and 27A-28B.

[0356] The information transmitted in the manner described herein may include, but is not limited to, the operating mode of the MPS device 810, the number and type of further devices 810, ambient object sensor information, and load condition monitoring information, such as battery charge status, load voltage, and load current.

[0357] The electronic circuit of the sealed bidirectional power transmission circuit device 800 may be implemented in various device manufacturing techniques, including, but not limited to, as a number of discrete elements on a suitable circuit board, as a hybrid circuit in which devices manufactured from different individual segments of a semiconductor material may be bonded or mounted on a suitable substrate material, as...

Claims

1. First and second self-synchronous high-frequency rectifiers / amplifiers configured to extract first and second high-frequency (HF) power signals from a DC power supply at first and second frequencies, respectively, An HF power link system configured to receive and mix the first and second HF power signals to generate a transferred power signal, A power transmission system for transmitting power between a DC power source and a variable load, comprising the HF power link system and a power signal conversion circuit configured to communicate with the variable load, generate an output power signal based at least partially on the transmitted power signal, and supply the output power signal to the variable load.

2. The system according to claim 1, further comprising an HF switching signal generator configured to supply first and second switching signals to the first and second rectifiers / amplifiers at first and second frequencies, respectively, and to establish and control the mutual phase relationship between the first and second switching signals.

3. The system according to claim 2, wherein the power signal conversion circuit includes a switch-mode rectifier configured to receive the power signal transferred from the HF power link system and rectify the transferred power signal to generate a rectified power signal, and a decompression circuit configured to receive the rectified power signal from the switch-mode rectifier and decompress the rectified power signal to generate an output power signal.

4. The system according to claim 3, wherein the first and second self-synchronous high-frequency rectifiers / amplifiers are configured to operate in rectification mode, and the switch-mode rectifier is configured to operate in always-on mode, thereby extracting power from the variable load and transferring it to a DC power supply via the power signal conversion circuit and the HF power link system.

5. The first frequency and the second frequency are the same frequency. The system according to claim 2, characterized in that the first and second switching signals have a relative phase difference that can be adjusted by the HF switching signal generator.

6. The system according to claim 5, wherein the HF switching signal generator is configured to adjust the relative phase difference between the first switching signal and the second switching signal based on the DC level in the variable load, thereby generating the power transmitted from the HF power link system as a DC signal with adjusted amplitude.

7. The system according to claim 5, wherein the HF switching signal generator is configured to modulate the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived at the frequency of the power signal of the variable load, at least in part on a modulation function, and generates a power signal transmitted from the HF power link system as an AC power signal modulated at the frequency of the power signal of the variable load.

8. The system according to claim 2, wherein the first and second frequencies differ by only the difference frequency.

9. The system according to claim 8, wherein the HF switching signal generator is configured to determine the first and second frequencies and set the difference frequency to twice the frequency of the power signal in the variable load.

10. The HF power link system is configured to generate power signals transmitted at differential frequencies, and The power signal conversion circuit is configured to supply an output power signal to the variable load at the frequency of the power signal in the variable load, according to claim 8.

11. The system according to claim 1, wherein the HF power link system includes a wireless power link.

12. The wireless HF power link system is the system according to claim 11, which includes a bimodal wireless HF power link system.

13. The HF power link system is the system according to claim 1, which includes a wired HF power link.

14. The steps include: extracting corresponding first and second HF power signals from a DC power supply at first and second high-frequency (HF) frequencies via corresponding first and second self-synchronous high-frequency rectifiers / amplifiers; In an HF power link system, the steps include receiving and mixing the first and second HF power signals to generate a transferred power signal, In a power signal conversion circuit that communicates with the HF power link system and a variable load, the steps include generating an output power signal based at least partially on the transferred power signal, A method for transmitting power between a DC power supply and a variable load, comprising the step of supplying an output power signal to the variable load.

15. In an HF switching signal generator that communicates with the first and second rectifiers / amplifiers, the steps include generating first and second switching signals at first and second frequencies, respectively, The method according to claim 11, further comprising the step of establishing and controlling the mutual phase relationship between the first switching signal and the second switching signal in an HF switching signal generator.

16. In the switch-mode rectifier of the power signal conversion circuit, the steps include receiving and rectifying the power signal transferred from the HF power link system. The method according to claim 11, further comprising the step of receiving and unfolding a power signal rectified from the switch-mode rectifier in the unfolding circuit of the power signal conversion circuit.

17. The steps of setting the first and second self-synchronous high-frequency rectifiers / amplifiers to rectification mode, The steps include setting the switch-mode rectifier to a permanently on mode and The steps of extracting power from the variable load and The method according to claim 16, further comprising the step of transferring the extracted power to the DC power supply via the power signal conversion circuit and the HF power link system.

18. The method according to claim 15, wherein the transfer of the power signal in the HF power link system includes the wireless transfer of the power signal.

19. The method according to claim 18, wherein the transfer of the power signal at high frequency in the HF power link system includes the transfer of the power signal bimodally and wirelessly.

20. The method according to claim 15, wherein the transfer of the power signal in the HF power link system includes the transfer of the power signal via a wired connection.

21. The method according to claim 15, wherein the first and second frequencies of the first and second switching signals are the same frequency, and the first and second switching signals have a relative phase difference that can be adjusted by an HF switching signal generator.

22. The method according to claim 21, further comprising the step of adjusting the relative phase difference between the first switching signal and the second switching signal based on the DC level of the variable load to generate the power signal transmitted from the HF power link system as a DC signal with correspondingly adjusted amplitude.

23. The method according to claim 21, further comprising the step of modulating the mutual phase difference between the first switching signal and the second switching signal, at least in part on a modulation function, with a phase modulation frequency derived at the frequency of the power signal of the variable load, to generate a power signal transmitted from the HF power link system as an AC power signal modulated at the frequency of the power signal of the variable load.

24. The steps include determining the first and second frequencies of the corresponding first and second switching signals, The method according to claim 15, further comprising the step of setting the difference frequency to be equal to twice the frequency of the power signal in the variable load.

25. The steps include generating a power signal transmitted at the differential frequency from the HF power link system and The method according to claim 24, further comprising the step of supplying an output power signal to the variable load at the frequency of the power signal in the variable load.

26. Each is configured to extract corresponding pairs of first and second HF power signals from one of at least one DC power supplies, and the corresponding pairs of first and second HF power signals include at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers having corresponding pairs of first and second frequencies, An HF power link system configured to receive the first HF power signal and mix it with the corresponding pair of second HF power signals of the first and second HF power signals to generate a transfer power signal, It includes the HF power link system and a power signal conversion circuit that communicates with the variable load, The power signal conversion circuit is configured to generate an output power signal based at least partially on the transferred power signal and to supply the output power signal to the variable load. A power transmission system that transmits power between at least one direct current (DC) power source and a variable load.

27. The system further includes one or more HF switching signal generators configured to output one or more pairs of first and second switching signals, Each of the first and second self-synchronous high-frequency rectifiers / amplifiers is configured to receive one corresponding pair of one or more pairs of first and second switching signals, the corresponding pair of first and second switching signals includes a corresponding pair of first and second frequencies, Each of the one or more HF switching signal generators is configured to supply at least one pair of one or more pairs of first and second switching signals to a corresponding pair of at least one pair of first and second self-synchronizing high-frequency rectifiers / amplifiers, and to establish and control the mutual phase relationship between the first and second switching signals in the corresponding pair of one or more pairs of first and second switching signals. The system according to claim 26.

28. The aforementioned at least one DC power supply includes a single DC power supply, All pairs of at least one pair of the first and second self-synchronous high-frequency rectifiers / amplifiers communicate with a single DC power supply. The system according to claim 27, wherein the one or more HF switching signal generators include a single HF switching signal generator.

29. The aforementioned at least one DC power supply includes a plurality of DC power supplies, The first and second pairs of self-synchronous high-frequency rectifiers / amplifiers include a plurality of pairs of self-synchronous high-frequency rectifiers / amplifiers, each pair communicating with a corresponding one of a plurality of DC power supplies, and The system according to claim 27, wherein the one or more HF switching signal generators include a plurality of HF switching signal generators, each of the plurality of HF switching signal generators is configured to provide one pair of one or more pairs of first and second switching signals to one of a plurality of pairs of first and second self-synchronous high-frequency rectifiers / amplifiers.

30. All of the first switching signals in one or more pairs of the first and second switching signals have the same frequency. The system according to claim 27, wherein all of the first HF power signals corresponding to one or more pairs of the first and second power signals have the same frequency.

31. The system according to claim 26, wherein the power signal conversion circuit includes a switch-mode rectifier configured to receive the power signal transferred from the HF power link system and rectify the transferred power signal to generate a rectified power signal, and a decompression circuit configured to receive the rectified power signal from the switch-mode rectifier and decompress the rectified power signal to generate an output power signal.

32. The system according to claim 31, wherein in each pair of at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers, the first and second self-synchronous high-frequency rectifiers / amplifiers are configured to operate in rectification mode, and the switch-mode rectifier is configured to operate in always-on mode, thereby extracting power from the variable load to at least one DC power supply via the power signal conversion circuit and the HF power link system.

33. The HF power link system includes a wireless power link system, as described in claim 26.

34. The wireless HF power link system includes a bimodal wireless HF power link system, according to claim 33.

35. The HF power link system includes a wired power link system, as described in claim 26.

36. The system according to claim 27, wherein the first and second frequencies are the same within each pair of first and second frequencies, and the first and second switching signals within each pair of first and second switching signals have a relative phase difference between them that can be adjusted by one or more corresponding HF switching signal generators.

37. The system according to claim 36, wherein at least one of the one or more HF switching signal generators is configured to adjust the relative phase difference between the first switching signal and the second switching signal in at least one corresponding switching signal pair based on the DC voltage level of the variable load, thereby generating a power signal transmitted from the HF power link system as a DC signal whose amplitude is adjusted accordingly.

38. The system according to claim 36, wherein all of the one or more HF switching signal generators are configured to modulate the mutual phase difference between the first switching signal and the second switching signal in each switching signal pair at a phase modulation frequency derived from the frequency of the power signal in the variable load, at least in part on a modulation function, thereby generating a power signal transmitted from the HF power link system as an AC power signal modulated at the frequency of the power signal in the variable load.

39. The system according to claim 36, wherein all of the one or more HF switching signal generators are configured to modulate, at least partially, the phase difference between the first switching signal and the second switching signal in at least one of the plurality of switching signals with a phase modulation frequency derived from the frequency of the power signal in the variable load, based at least partially on a modulation function, thereby generating a power signal transmitted from the HF power link system as a DC power signal having a portion of the signal modulated with the frequency of the power signal in the variable load.

40. The system according to claim 36, wherein all of the first switching signals of one or more pairs of the first and second switching signals have the same phase, and all of the corresponding first HF power signals of the one or more pairs of HF power signals have the same phase.

41. The system according to claim 27, wherein the first and second frequencies in each frequency pair differ by only the difference frequency.

42. The system according to claim 41, wherein each of the one or more HF switching signal generators is configured to determine the first and second frequencies in each pair and to set the difference frequency in each pair to twice the frequency of the power signal of the variable load.

43. The system according to claim 41, wherein the HF power link system is configured to generate a power signal transmitted at a difference frequency, and the power signal conversion circuit is configured to supply an output power signal to the variable load at the frequency of the power signal in the variable load.

44. Steps include: extracting a corresponding pair of first and second high-frequency (HF) power signals from one of at least one DC power supplies using at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers, wherein the corresponding pair of first and second high-frequency (HF) power signals have the corresponding pair of first and second frequencies; The steps include receiving the corresponding pair of first and second HF power signals by an HF power link system, In the HF power link system, the steps include: mixing a first HF power signal with the second HF power signal of the corresponding pair of first and second HF power signals to generate a transfer power signal; The steps include generating an output power signal based at least partially on the transferred power signal using the HF power link system and a power signal conversion circuit that communicates with the variable load, Steps to supply the output power signal to the variable load. A method for transmitting power between at least one direct current (DC) power source and a variable load, including the above.

45. The steps include outputting one or more pairs of first and second switching signals from one or more HF switching signal generators, The steps of receiving a corresponding pair of one or more pairs of first and second switching signals by at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers, wherein the corresponding pair of first and second switching signals has a corresponding pair of first and second frequencies, The steps of supplying at least one pair of first and second HF switching signals from each of one or more pairs of HF switching signal generators to at least one pair of corresponding first and second self-synchronizing signal high-frequency rectifiers / amplifiers, The step of establishing and controlling the mutual phase relationship between the first and second switching signals in corresponding pairs of one or more pairs of first and second switching signals using one or more HF switching signal generators. The method according to claim 44, further comprising:

46. The aforementioned at least one DC power supply includes a single DC power supply, The at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers includes a plurality of self-synchronous high-frequency rectifiers / amplifiers, all of which communicate with a single DC power supply. The method according to claim 45, wherein the one or more HF switching signal generators include a single HF switching signal generator.

47. The method according to claim 45, wherein the at least one DC power supply comprises a plurality of DC power supplies, the at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers comprises a plurality of pairs of self-synchronous high-frequency rectifiers / amplifiers, each pair of the plurality of self-synchronous high-frequency rectifiers / amplifiers communicates with a corresponding one of the plurality of DC power supplies, and the one or more HF switching signal generators comprises a plurality of HF switching signal generators, each of the plurality of HF switching signal generators is configured to provide one pair of one or more pairs of first and second switching signals to a corresponding pair of the plurality of first and second self-synchronous high-frequency rectifiers / amplifiers.

48. The method according to claim 45, wherein all of the first switching signals of a plurality of pairs of first and second switching signals have the same frequency, and all of the corresponding first HF power signals of a plurality of pairs of first and second HF powers have the same frequency.

49. The power signal conversion circuit's switch-mode rectifier receives and rectifies a transfer power signal to an HF power link system, at least partially. In the unfolding circuit of a power signal conversion circuit, the step of receiving the rectified power signal from a switch-mode rectifier, unfolding it, and generating an output power signal is The method according to claim 44, further comprising:

50. The steps of setting at least one pair of first and second self-synchronous high-frequency rectifiers / amplifiers to rectification mode, The steps include setting the switch-mode rectifier to always-on mode, The steps of extracting power from the variable load and The step of transmitting the extracted power to at least one DC power supply via a power signal conversion circuit and an HF power link system is The method according to claim 49, further comprising:

51. The method according to claim 45, wherein the first and second frequencies within each pair of first and second frequencies are the same, and the first and second switching signals within each pair of first and second switching signals have a relative phase difference between them that can be adjusted by one or more corresponding HF switching signal generators.

52. At least one of the one or more HF switching signal generators further includes the step of adjusting the relative phase difference between the first switching signal and the second switching signal in at least one corresponding switching signal pair, at least in part, based on the DC voltage level of the variable load, to generate a power signal transmitted from the HF power link system as a DC signal whose amplitude is adjusted accordingly. The method according to claim 51, wherein the mutual phase difference is adjusted by at least one of the HF switching signal generators.

53. The method further includes the step of modulating the mutual phase difference between the first switching signal and the second switching signal within each pair of switching signals, at least in part, based on a modulation function, with a phase modulation frequency derived at the frequency of the power signal of the variable load, thereby generating the power signal transmitted from the HF power link system as an AC power signal modulated at the frequency of the power signal of the variable load. The method according to claim 51, wherein the mutual phase difference is adjusted by all of one or more of the HF switching signal generators.

54. The method further includes the step of modulating the phase difference between the first switching signal and the second switching signal in at least one of a plurality of pairs of switching signals, based at least in part on a modulation function, with a phase modulation frequency derived at the frequency of the power signal of the variable load, thereby generating a DC power signal having a portion of the signal modulated at the frequency of the power signal of the variable load transmitted from the HF power link system. The method according to claim 51, wherein the mutual phase difference is adjusted by at least one of the HF switching signal generators.

55. The method according to claim 51, wherein all of the first switching signals of the plurality of pairs of first and second switching signals have the same phase, and all of the corresponding first power signals of the plurality of pairs of HF power signals have the same phase.

56. The method according to claim 45, wherein the first and second frequencies in each pair of first and second frequencies differ by only a difference frequency.

57. The steps include determining the first and second frequencies in each pair of corresponding first and second switching signals, and The step of setting the difference frequency for each pair to twice the frequency of the power signal of the variable load. The method according to claim 56, further comprising:

58. The steps include generating a power signal transmitted at the differential frequency from the HF power link system, The step of supplying an output power signal to the variable load at the frequency of the power signal within the variable load. The method according to claim 56, further comprising:

59. The method according to claim 44, wherein the transfer of the power signal in the HF power link system includes the wireless transfer of the power signal.

60. The method according to claim 59, wherein wirelessly transferring the power signal in the HF power link system includes wirelessly transferring the power signal bimodally.

61. The method according to claim 44, wherein the transfer of the power signal in the HF power link system includes the transfer of the power signal via a wired connection.

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