Power Conversion Device

Abstract

To provide a technology that suppresses the magnetic bias of a transformer without using an additional component for preventing magnetic bias, and enables high efficiency and miniaturization of an insulated bidirectional DC / DC converter.SOLUTION: A control device of a power conversion device outputs a first reference control signal for turning ON or OFF a first switching element to the first switching element and a third switching element of a first full bridge circuit when the boosting operation is performed, outputs a first reference inversion signal obtained by inverting the phase of the first reference control signal to a second switching element and a fourth switching element, extends a period in which at least the second switching element and the fourth switching element of the second switching leg are turned off at the same time, and makes the period longer than a period in which the first switching element and the third switching element of the first switching leg are simultaneously turned off.SELECTED DRAWING: Figure 16

Description

[Technical Field]

[0001] The present invention relates to a DAB type power conversion device capable of step-up and step-down operations. [Background technology]

[0002] Conventionally, a DAB (Dual Active Bridge) isolated bidirectional DC / DC converter has been proposed as a power conversion device, which has full-bridge circuits on both the primary and secondary sides of a transformer and is capable of step-up and step-down operations. In a DAB isolated bidirectional DC / DC converter, a challenge is how to suppress bias magnetism caused by DC current components generated in the transformer during step-up and step-down operations (see, for example, Patent Documents 1 and 2).

[0003] If biased magnetism occurs in a transformer due to DC current components, the biased magnetism component can cause magnetic saturation in the transformer core, potentially resulting in overcurrent. To suppress such biased magnetism, adding a capacitor to prevent biased magnetism or inserting a resistor in series is one possible solution, but adding these components inevitably increases loss, increases the size of the isolated bidirectional DC / DC converter, and increases manufacturing costs. [Prior art documents] [Patent documents]

[0004] [Patent Document 1] Japanese Patent Application Laid-Open No. 2010-93938 [Patent Document 2] Japanese Patent Application Publication No. 2019-118234 Summary of the Invention [Problem to be solved by the invention]

[0005] The present invention has been made in light of the above circumstances, and its purpose is to provide a technology that suppresses magnetism bias in a transformer without using additional components for preventing magnetism bias, thereby enabling high-efficiency and miniaturization of isolated bidirectional DC / DC converters. [Means for solving the problem]

[0006] One aspect of the disclosed technology for solving the above problem is: a DC / DC converter including: a first full-bridge circuit including a first switching leg and a second switching leg connected in parallel to a first input / output terminal pair; a second full-bridge circuit including a third switching leg and a fourth switching leg connected in parallel to a second input / output terminal pair; and a transformer including one winding connected to the first full-bridge circuit and the other winding connected to the second full-bridge circuit; a control unit that controls the DC / DC converter, the first switching leg has a first switching element and a third switching element, a source terminal of the first switching element and a drain terminal of the third switching element are connected in series at a first connection point, and a drain terminal of the first switching element and a source terminal of the third switching element are connected to the first input / output terminal pair; the second switching leg has a second switching element and a fourth switching element, a source terminal of the second switching element and a drain terminal of the fourth switching element are connected in series at a second connection point, and a drain terminal of the second switching element and a source terminal of the fourth switching element are connected to the first input / output terminal pair; the third switching leg includes a fifth switching element and a seventh switching element, a source terminal of the fifth switching element and a drain terminal of the seventh switching element are connected in series at a third connection point, and a drain terminal of the fifth switching element and a source terminal of the seventh switching element are connected to the second input / output terminal pair; the fourth switching leg includes a sixth switching element and an eighth switching element, a source terminal of the sixth switching element and a drain terminal of the eighth switching element are connected in series at a fourth connection point, and a drain terminal of the sixth switching element and a source terminal of the eighth switching element are connected to the second input / output terminal pair; one winding of the transformer is connected to a first connection point of the first switching leg and a second connection point of the second switching leg, and the other winding of the transformer is connected to a third connection point of the third switching leg and a fourth connection point of the fourth switching leg; The control unit When a boost operation is performed, a first reference control signal is output to the first switching element and the third switching element of the first full bridge circuit, for turning the first switching element on or off; a first reference inverted signal obtained by inverting the phase of the first reference control signal is output to the second switching element and the fourth switching element; extending a period during which at least the second switching element and the fourth switching element of the second switching leg are simultaneously turned off, so as to be longer than a period during which the first switching element and the third switching element of the first switching leg are simultaneously turned off; It is characterized by:

[0007] As a result, when a magnetization bias occurs in the transformer TR, the power conversion device can suppress the magnetization bias by adjusting the dead time of each switching element related to the boost switching on a leg-by-leg basis. For example, the power conversion device can control the dead time so that it is longer only during the period when the transformer current flowing through the transformer TR is discontinuous (a section where the current value is zero). This can control the voltage applied to the excitation inductance Lm so that the DC component of the excitation current is reduced while suppressing relative loss reduction. This ensures a section where the current value becomes zero when the transformer current flowing through the transformer TR transitions from positive to negative and from negative to positive. This suppresses magnetization bias in the transformer without using additional components to prevent magnetization bias, providing a technology that enables high-efficiency and compact isolated bidirectional DC / DC converters.

[0008] In the present invention, when a first phase shift amount is a delay amount from when the second switching element falls from ON to OFF until when the seventh switching element of the third switching leg falls from ON to OFF, the control unit may vary a period during which the fifth switching element and the seventh switching element of the third switching leg are simultaneously turned OFF in accordance with the first phase shift amount, thereby suppressing output fluctuations when switching operation from the step-up mode to the step-down mode.

[0009] In addition, in the present invention, when a delay amount from when the fourth switching element falls from ON to OFF until when the eighth switching element of the fourth switching leg falls from ON to OFF is defined as a second phase shift amount, a period during which the sixth switching element and the eighth switching element of the fourth switching leg are simultaneously turned OFF may be varied according to the second phase shift amount, thereby suppressing output fluctuations when switching operation from the step-up mode to the step-down mode.

[0010] In addition, in the present invention, when a step-down operation is performed, the control unit uses a control signal for turning on or off the fourth switching element of the first full bridge circuit as a second reference control signal, and outputs the second reference control signal to the fourth switching element of the first full bridge circuit and outputs a second reference inverted signal, the second reference control signal being the inverted phase of the second reference control signal, to the second switching element when a delay amount from when the fourth switching element falls from on to off until when the third switching element of the first switching leg falls from on to off is a third phase shift amount, a third reference control signal delayed by the third phase shift amount from the second reference control signal to the third switching element of the first switching leg; a third reference inverted signal having an inverted phase of the third reference control signal to the first switching element; and a period during which at least the first switching element and the third switching element of the first switching leg are simultaneously turned off may be made shorter than a period during which the second switching element and the fourth switching element of the second switching leg are simultaneously turned off.

[0011] As a result, when a magnetization bias occurs in the transformer TR, the power conversion device can suppress the magnetization bias by adjusting the dead time of each switching element related to the step-down switching on a leg-by-leg basis. For example, the power conversion device can control the dead time to be longer only during the period when the transformer current flowing through the transformer TR is discontinuous (a section where the current is zero), thereby controlling the voltage applied to the excitation inductance Lm so that the DC component of the excitation current is reduced while suppressing relative loss reduction. Even when step-down switching is performed, it is possible to ensure a section where the current value becomes zero when the transformer current flowing through the transformer TR transitions from positive to negative and from negative to positive. This allows for the suppression of transformer magnetization bias without the use of additional components for preventing magnetization bias, providing a technology that enables high-efficiency and compact isolated bidirectional DC / DC converters.

[0012] In the present invention, the control unit may vary a period during which the fifth switching element and the seventh switching element of the third switching leg are simultaneously turned off in accordance with the third phase shift amount. The control unit may also vary a period during which the sixth switching element and the eighth switching element of the fourth switching leg are simultaneously turned off in accordance with the third phase shift amount. This makes it possible to suppress output fluctuations when switching operation from the buck mode to the boost mode. [Effects of the Invention]

[0013] The present invention provides a technology that can suppress biased magnetization of a transformer without using additional components for preventing biased magnetization, thereby enabling high efficiency and miniaturization of isolated bidirectional DC / DC converters. [Brief explanation of the drawings]

[0014] [Figure 1] 1 is a diagram showing a schematic configuration of a power conversion device 1 according to an embodiment of the present invention. [Figure 2] FIG. 1 is a schematic block diagram of a DC / DC converter for explaining biased magnetism, which is a premise of the present invention. [Figure 3] 4 is a time chart illustrating the transition of control during boost converter operation of the DC / DC converter that is the premise of the present invention. [Figure 4] FIG. 10 is a diagram illustrating bias magnetism in a simplified circuit model of a transformer according to an embodiment of the present invention. [Figure 5] 2 is a diagram showing a current flow in a DC / DC converter functioning as a boost converter according to an embodiment of the present invention. FIG. [Figure 6] FIG. 10 is a diagram illustrating a current flow when the dead time of leg 2 is relatively short according to an embodiment of the present invention. [Figure 7] FIG. 10 is a diagram illustrating a current flow when the dead time of leg 2 is relatively long according to an embodiment of the present invention. [Figure 8] FIG. 3 is a diagram illustrating a current path in a boost mode of the power conversion device according to the embodiment of the present invention. [Figure 9] 3A and 3B are diagrams illustrating current paths in the switching step-up mode at minimum TΦ and step-down mode at maximum TΦ in the power conversion device according to the embodiment of the present invention. [Figure 10] 4 is a graph showing changes in current at minimum TΦ in step-up mode and maximum TΦ in step-down mode of the power conversion device according to the embodiment of the present invention. [Figure 11] FIG. 3 is a diagram illustrating a current path in a boost mode of the power conversion device according to the embodiment of the present invention. [Figure 12]3A and 3B are diagrams illustrating current paths at minimum TΦ in step-up mode and maximum TΦ in step-down mode of the power conversion device according to the embodiment of the present invention. [Figure 13] 4 is a graph showing changes in current at minimum TΦ in step-up mode and maximum TΦ in step-down mode of the power conversion device according to the embodiment of the present invention. [Figure 14] 4 is a graph showing changes in current in a step-up mode and a step-down mode of the power conversion device according to the embodiment of the present invention. [Figure 15] 4 is a graph illustrating the transition of the phase shift amount when switching between step-up and step-down voltages in the power conversion device according to the embodiment of the present invention. [Figure 16] 4 is a timing chart showing transition of a control state in boost switching of a power conversion device according to an embodiment of the present invention. [Figure 17] 4 is a timing chart showing transition of a control state in step-down switching of a power conversion device according to an embodiment of the present invention. DETAILED DESCRIPTION OF THE INVENTION

[0015] [Application example] Hereinafter, application examples of the present invention will be described with reference to the drawings. Fig. 1 is a diagram showing a schematic configuration of a power conversion device 1 according to an application example of the present invention. The power conversion device 1 according to this application example has a DAB (Dual Active Bridge) DC / DC converter 10 and is capable of bidirectional power conversion via a transformer TR. The power conversion device 1 includes a control unit 20 that controls the DC / DC converter 10 (the ON / OFF of each switching element in the DC / DC converter 10) by changing the level of a control signal sent to each switching element in the DC / DC converter 10.

[0016] The control unit 20 is configured (programmed) to determine whether the DC / DC converter 10 should operate as one of the following four types of converters based on the input data (current value, voltage value), and to control the DC / DC converter 10 so that it operates as the determined converter. The first input / output terminal pair 13 is the primary side of the boost converter The first input / output terminal pair 13 is the primary side of the step-down converter The second input / output terminal pair 14 is the primary side of the boost converter The second input / output terminal pair 14 is the primary side of the step-down converter The control unit 20 is also configured (programmed) to instantly change the control content for the DC / DC converter 10 (such as changing from control that causes the DC / DC converter 10 to operate as a step-up converter on the primary side of the first input / output terminal pair 13 to control that causes the DC / DC converter 10 to operate as a step-down converter on the primary side of the second input / output terminal pair 14).

[0017] 2 to 4, there are individual differences between devices in terms of switching during step-up and step-down conversion among the switching elements (Q1-Q8) that make up the DC / DC converter 10. For this reason, during power conversion (step-up conversion, step-down conversion), a DC component caused by the individual differences between the switching elements (Q1-Q8) that make up the DC / DC converter 10 may occur in the transformer TR.

[0018] In the power conversion device 1 according to this embodiment, when biased magnetism occurs in the transformer TR, the dead time of each switching element related to the step-up switching and step-down switching is controlled for each leg to suppress the biased magnetism. Specifically, as shown in Figs. 16 and 17, the length of the dead time is increased or decreased for each leg so that the DC component included in the excitation current flowing through the excitation inductance Lm of the transformer TR is reduced, thereby controlling the voltage applied to the excitation inductance Lm. This makes it possible to suppress the biased magnetism without using additional components for preventing biased magnetism. We can provide technology that suppresses biased magnetism in transformers and enables high efficiency and miniaturization of isolated bidirectional DC / DC converters.

[0019] Example 1 Hereinafter, specific embodiments of the present invention will be described in more detail with reference to the drawings. Note that the configurations of the embodiments shown below are examples, and the disclosed technology is not limited to the configurations of the embodiments.

[0020] <Configuration of power conversion device> FIG. 1 is a diagram illustrating a schematic configuration of a power conversion device 1 according to a first embodiment of the present invention. The power conversion device 1 according to this embodiment has a DAB (Dual Active Bridge) DC / DC converter 10 and is capable of bidirectional power conversion via a transformer TR. As illustrated, the power conversion device includes the DC / DC converter 10, a control unit 20, a first input / output terminal pair 13 (13p, 13m), and a second input / output terminal pair 14 (14p, 14m). In the first input / output terminal pair 13 and the second input / output terminal pair 14, the input / output terminals 13p, 14p are high-potential side input / output terminals, and the input / output terminals 13m, 14m are low-potential side input / output terminals. A capacitor C1 for smoothing input / output voltages is connected between the input / output terminals 13m, 13p. Similarly, a capacitor C2 for smoothing input / output voltages is connected between the input / output terminals 14m, 14p. An electrolytic capacitor is exemplified as the capacitors C1 and C2.

[0021] DC / DC converter 10 is an isolated bidirectional DC / DC converter whose main components are a transformer TR, two reactors Lr1 and Lr2, and two full-bridge circuits 11 and 12. Hereinafter, the left-side full-bridge circuit 11 and the right-side full-bridge circuit 12 in FIG. 1 will also be referred to as the first full-bridge circuit 11 and the second full-bridge circuit 12, respectively. Similarly, the left-side reactor Lr1 and the right-side reactor Lr2 in FIG. 1 will also be referred to as the first reactor Lr1 and the second reactor Lr2, respectively. Furthermore, the winding Wn1 connected to full-bridge circuit 11 of transformer TR and the winding Wn2 connected to full-bridge circuit 12 will also be referred to as the first winding Wn1 and the second winding Wn2, respectively. The first reactor Lr1 and the second reactor Lr2 may utilize the leakage inductance of the first winding Wn1 connected to the full bridge circuit 11 of the transformer TR and the second winding Wn2 connected to the full bridge circuit 12, respectively. The transformer TR of the DC / DC converter 10 does not need to have a turns ratio of 1:1. However, the following description of the configuration and operation of the power conversion device 1 will be given assuming that the turns ratio of the transformer TR is 1:1.

[0022] The first full-bridge circuit 11 of the DC / DC converter 10 includes a first leg L1 having a first switching element Q1 and a third switching element Q3 connected in series, and a second leg L2 having a second switching element Q2 and a fourth switching element Q4 connected in series. As shown in the figure, an n-th diode Dn (n = 1 to 4) is connected in parallel between the drain terminal and the source terminal of the n-th switching element Qn (n = 1 to 4) of each leg. Each leg is connected to a first input / output terminal pair 13. The drain terminal of the first switching element Q1 and the drain terminal of the second switching element Q2 are connected to an input / output terminal 13p, and the source terminal of the third switching element Q3 and the source terminal of the fourth switching element Q4 are connected to an input / output terminal 13m. A connection point p1 of the first leg L1, where the source terminal of the first switching element Q1 and the drain terminal of the third switching element Q3 are connected, is connected to one end of the first winding Wn1 of the transformer TR via a first reactor Lr1. A connection point p2 of the second leg L2, where the source terminal of the second switching element Q2 and the drain terminal of the fourth switching element Q4 are connected, is connected to the other end of the first winding Wn1 of the transformer TR.

[0023] The second full-bridge circuit 12 of the DC / DC converter 10 includes a third leg L3 having a fifth switching element Q5 and a seventh switching element Q7 connected in series, and a fourth leg L4 having a sixth switching element Q6 and an eighth switching element Q8 connected in series. As shown in the figure, an nth diode Dn (n = 5 to 8) is connected in parallel between the drain and source terminals of the nth switching element Qn (n = 5 to 8) of each leg. Both the third leg L3 and the fourth leg L4 are connected to a second input / output terminal 14. The drain terminal of the fifth switching element Q5 and the drain terminal of the sixth switching element Q6 are connected to an input / output terminal 14p, and the source terminal of the seventh switching element Q7 and the source terminal of the eighth switching element Q8 are connected to an input / output terminal 14m. Furthermore, a connection point p3 of the third leg L3, where the source terminal of the fifth switching element Q5 and the drain terminal of the seventh switching element Q7 are connected, is connected to one end of the second winding Wn2 of the transformer TR via a second reactor Lr2. A connection point p4 of the fourth leg L4, where the source terminal of the sixth switching element Q6 and the drain terminal of the eighth switching element Q8 are connected, is connected to the other end of the second winding Wn2 of the transformer TR. Hereinafter, the "nth switching element Qn (n = 1 to 8)" will also be referred to simply as the "switching element Qn (n = 1 to 8)," and the "nth diode Dn (n = 1 to 8)" will also be referred to simply as the "diode Dn (n = 1 to 8)." The diode Dn (n = 1 to 8) may be an internal diode of the switching element Qn (n = 1 to 8) or an external diode.

[0024] The semiconductor materials for the switching elements Q1 to Q8 may include, but are not limited to, gallium nitride (GaN), silicon (Si), silicon carbide (SiC), etc. The semiconductor switching elements may include MOSFETs (Metal Oxide Semiconductor Field Effect Transistors), IGBTs (Insulated Gate Bipolar Transistors), etc. Diodes D1 to D8 are connected in anti-parallel to these semiconductor switching elements used as the switching elements Q1 to Q8.

[0025] Voltage sensors 15p and 15s for measuring the magnitude of input and output voltages are provided at the first input / output terminal pair 13 and the second input / output terminal pair 14 of the DC / DC converter 10. Note that the DC / DC converter 10 may be provided with various sensors for measuring the magnitude of input and output currents.

[0026] The control unit 20 controls the DC / DC converter 10 (ON / OFF of each switching element in the DC / DC converter 10) by changing the level of a control signal to each switching element in the DC / DC converter 10. Hereinafter, the control signal for the nth switching element Qn (n = 1 to 8) will also be referred to as the control signal Gn. The control signal Gn generated by the control unit 20 is input to the gate terminal of the corresponding nth switching element Qn (n = 1 to 8). The control unit 20 is composed of a processor such as a microcontroller, a gate driver, etc., and receives as input the outputs of the various sensors (voltage sensors 15p, 15s, etc.) described above.

[0027] The control unit 20 is configured (programmed) to determine whether the DC / DC converter 10 should operate as one of the following four types of converters based on the input data (current value, voltage value), and to control the DC / DC converter 10 so that it operates as the determined converter. The first input / output terminal pair 13 is the primary side of the boost converter The first input / output terminal pair 13 is the primary side of the step-down converter The second input / output terminal pair 14 is the primary side of the boost converter The second input / output terminal pair 14 is the primary side of the step-down converter

[0028] The control unit 20 also changes the control content of the DC / DC converter 10 (DC The DC / DC converter 10 is also configured (programmed) to instantly change control from a control that causes the first input / output terminal pair 13 side to operate as a primary side step-up converter to a control that causes the second input / output terminal pair 14 side to operate as a primary side step-down converter.

[0029] (Regarding transformer bias magnetism) First, we will explain the biased magnetization that occurs in the transformer TR of the DC / DC converter 10 using Figures 2 to 4. Figure 2 is a schematic block diagram of the DC / DC converter 10 to explain the biased magnetization. In Figure 2, "RL" represents the impedance of the transformer TR during switching operation, and "Lm" represents the excitation inductance of the transformer TR during switching operation. Furthermore, "Ip," "Im," and "Is," indicated by dashed arrows, represent the current flowing through the impedance RL, the excitation current flowing through the excitation inductance Lm, and the current flowing through the second reactor Lr2 (or the leakage inductance on the secondary side), respectively. Furthermore, "Vt" and "Vl," indicated by solid arrows, represent the voltage applied to the first reactor Lr1 (or the leakage inductance on the primary side) and the voltage applied to the excitation inductance Lm. The arrow directions of the dashed and solid arrows represent the direction of current flow and the direction of voltage application. In the DC / DC converter 10 shown in FIG. 2, an input voltage Vi applied to a first input / output terminal pair 13 is boosted by the switching operations of switching elements Q1 to Q4 of a first full-bridge circuit 11 and switching elements Q5 to Q8 of a second full-bridge circuit 12, and is output to a second input / output terminal pair 14 as an output voltage Vo.

[0030] Figure 3 is a time chart illustrating the transition of control during boost converter operation of DC / DC converter 10. Figure 3(a) shows a graph illustrating the transition of current flowing through transformer TR, with the vertical axis representing the magnitude of the current (A) and the horizontal axis representing the passage of time. The dashed line in Figure 3(a) shows the transition of current (Itr1) flowing through first reactor Lr1 during boost converter operation, and the solid line shows the transition of current (Itr3) flowing through second reactor Lr2.

[0031] 3(b) and 3(c) are graphs showing transitions of control signals at the gate terminals of switching elements Qn (n=1 to 8). The solid line in FIG. 3(b) shows transitions of the voltage values ​​(Vg2, Vg3) of the control signals input to the gate terminals of switching elements Q2 and Q3 in the first full-bridge circuit 11, while the dashed line shows transitions of the voltage value (Vg7) of the control signal input to the gate terminal of switching element Q7 in the second full-bridge circuit 12. The control signal input to the gate terminal of switching element Q7 is controlled to rise, for example, a predetermined period after the rise of the control signal input to the gate terminals of switching elements Q2 and Q3 in the first full-bridge circuit 11. In DC / DC converter 10, the predetermined period is changed so that the output voltage Vo and output current output after boosting reach target values.

[0032] The solid line in FIG. 3(c) shows the transition of the voltage value (Vg1, Vg4) of the control signal input to the gate terminals of switching elements Q1 and Q4 in the first full-bridge circuit 11, while the dashed line shows the transition of the voltage value (Vg8) of the control signal input to the gate terminal of switching element Q8 in the second full-bridge circuit 12. In FIG. 3(c) as well, the control signal input to the gate terminal of switching element Q8 is controlled to rise, for example, a predetermined period after the rising edge of the control signal input to the gate terminals of switching elements Q1 and Q4 in the first full-bridge circuit 11. In DC / DC converter 10, the predetermined period is changed so that the output voltage Vo and output current output after boosting reach target values. In FIGS. 3(b) and 3(c), switching elements Q5 and Q6 are controlled to be OFF (the drain terminal and source terminal are open).

[0033] FIG. 3(d) is a graph showing the transitions of the voltage (Vtr2) at the magnetizing inductance Lm and the current (Itr2) flowing through the magnetizing inductance Lm. In FIG. 3(d), the transitions of the voltage (Vtr2) at the magnetizing inductance Lm are represented by the dashed line, and the transitions of the current (Itr2) flowing through the magnetizing inductance Lm are represented by the solid line. As shown by the dashed line in FIG. 3(d), the voltage value of the voltage (Vtr2) at the magnetizing inductance Lm of the transformer TR changes in a step-like manner in predetermined steps due to the switching operation of the switching elements Q1 to Q8. It is also clear that the current (Itr2) flowing through the magnetizing inductance Lm, shown by the solid line, also changes sinusoidally within a predetermined range (±1.5 A in FIG. 3(d)) in accordance with the switching operation of the switching elements Q1 to Q8. In a DAB DC / DC converter 10, as shown in Figures 3(a) to 3(d), when power conversion is performed using ideal switching, the average value of the excitation current Im is zero, and biased magnetization due to DC components does not occur. However, the switching elements (Q1-Q8) that make up the DC / DC converter 10 have individual differences in switching during step-up and step-down conversion. Therefore, during power conversion (step-up conversion, step-down conversion), DC components due to individual differences in the switching elements (Q1-Q8) that make up the DC / DC converter 10 may occur in the transformer TR.

[0034] 4A and 4B are diagrams illustrating biased magnetization in a simplified circuit model of a transformer TR. Fig. 4A shows a circuit model in which the other end of the impedance R and one end of the excitation inductance Lm are connected in series, and a voltage Vin is applied between the one end of the impedance R and the other end of the excitation inductance Lm. In the circuit model of Fig. 4A, the voltage Vin changes due to switching of the switching elements Qn (n=1 to 8), and the voltage Vt applied to the excitation inductance Lm and the excitation current Im change accordingly.

[0035] Figure 4(b) is a diagram illustrating the state in which ideal switching is performed in the circuit model of Figure 4(a). The vertical axis of Figure 4(b) represents the relative magnitude of the current or voltage, and the horizontal axis represents the passage of time. The solid line in Figure 4(b) represents the transition of the voltage Vt applied to the magnetizing inductance Lm due to switching, and the dashed line represents the transition of the current Im flowing through the magnetizing inductance Lm due to switching. The voltage Vt applied to the magnetizing inductance Lm changes symmetrically between positive and negative within a specified range (±Vin) due to switching. If the switching cycle is "T," then the voltage Vt changes in a rectangular pattern from "-Vin" to "+Vin" every cycle "T / 2." The current Im flowing through the magnetizing inductance Lm also changes in a triangular wave shape that is symmetrical in both positive and negative directions, reaching a positive peak value when the voltage Vt reaches the voltage value "+Vin" and a negative peak value when the voltage Vt reaches the voltage value "-Vin." In this way, when ideal switching is performed, the current Im flowing through the magnetizing inductance Lm changes symmetrically in both positive and negative directions, and the DC component is zero.

[0036] Figure 4(c) is a diagram that explains the case where deviations in switching timing occur due to individual differences in the circuit model of Figure 4(a). The vertical and horizontal axes, solid and dashed lines in Figure 4(c) are the same as those in Figure 4(b). Due to individual differences between the switching elements (Q1-Q8), deviations in switching timing during power conversion may occur. Such switching deviations appear as a deviation (delay) in the timing of switching from conduction to open between the drain terminal and source terminal within the switching period (T). The amount of deviation (delay) within this switching period is referred to as "Td."

[0037] As shown in the solid line graph in Figure 4(c), at the timing when the drain terminal-source terminal switches from conductive to open, the delay amount Td is added to the period (T / 2), and the switching The conduction period between the drain and source terminals within the switching period (T) becomes relatively long, as shown by "T / 2 + Td." Meanwhile, when the drain and source terminals switch from open to conductive, the delay Td is subtracted from the period (T / 2), and the open period between the drain and source terminals within the switching period (T) becomes relatively short, as shown by "T / 2 - Td." In the transformer TR, the current due to the applied voltage Vt during the conduction period corresponding to the delay Td appears as a DC component Idc across the magnetizing inductance Lm. This DC component is then superimposed on the positive voltage value as a voltage drop of "R × Idc" through the impedance R. In an ideal state, a voltage drop occurs in the voltage Vt, which changes symmetrically within the range of "+Vin" to "-Vin," and an asymmetric voltage that changes within the range of "+Vin - R × Idc" to "-Vin" is applied to the magnetizing inductance Lm.

[0038] Furthermore, as shown in Fig. 4(c), an excitation current Im flows through the excitation inductance Lm in which the DC component Idc is generated, and the excitation current Im changes asymmetrically between positive and negative, reaching a positive peak value when the voltage Vt reaches the voltage value "+Vin" and a negative peak value when the voltage Vt reaches the voltage value "-Vin." Note that in Fig. 4(c), the current flowing through the excitation inductance Lm changes as a triangular wave current that is inflated on the positive side due to the superposition of the positive DC component Idc.

[0039] (Suppression of biased magnetism) Next, suppression of biased magnetism occurring in the transformer TR of the DC / DC converter 10 in this embodiment will be described using Figures 5 to 7. Figure 5 is a diagram showing the flow of current in the DC / DC converter 10 functioning as a boost converter. Each switching element of the DC / DC converter 10 is subjected to voltage control applied to the gate terminal shown in Figures 3(b) and 3(c) to establish conduction (also referred to as "ON") or open (also referred to as "OFF") between the drain terminal and the source terminal, boosting the input voltage Vi applied to the first input / output terminal pair 13 and outputting the output voltage Vo to the second input / output terminal pair 14.

[0040] In FIG. 5, the current flow indicated by the thick dashed-dotted arrows represents current Itr1 flowing through the first full-bridge circuit 11 and the primary side of the transformer TR, while the current flow indicated by the thick solid arrows represents current Itr3 flowing through the secondary side of the transformer TR and the second full-bridge circuit 12. The dashed arrows represent excitation current Itr2 flowing through the excitation inductance. Note that FIG. 5 assumes that a magnetic bias has occurred in the transformer TR, and describes a state in which the polarity of excitation current Itr2 changes. That is, FIG. 5 illustrates a state immediately after the control state shown in FIG. 3(b) has been changed from the state shown in FIG. 3(c), in which switching elements Q1 and Q4 are ON in the first full-bridge circuit 11 and switching element Q8 is ON in the second full-bridge circuit 12. In this state, switching element Q8 is ON. In the control state shown in FIG. 3(b), the switching elements Q2 and Q3 of the first full-bridge circuit 11 are turned ON, the switching element Q8 of the second full-bridge circuit 12 is switched from ON to OFF, and the switching element Q7 is controlled to be turned ON.

[0041] As indicated by the thick dashed-dotted arrow, current Itr1 flows in the following order: transformer TR (primary side), node p2, switching element Q2, input / output terminal 13p, input voltage Vi, input / output terminal 13m, switching element Q3, node p1, impedance RL, first reactance Lr1, and transformer TR (primary side). Furthermore, because switching element Q8 remains ON, current Itr3 flows in the following order: transformer TR (secondary side), second reactance Lr2, node p3, switching element Q5 (diode D5), input / output terminal 14p, output voltage Vo, input / output terminal 14m, switching element Q8, node p4, and transformer TR (secondary side).

[0042] Here, a dead time is set for each switching element constituting each of the first full-bridge circuit 11 and the second full-bridge circuit 12 to prevent arm short-circuiting. That is, the switching elements Q1 and Q3 constituting the first leg L1 of the first full-bridge circuit 11 and the switching elements Q2 and Q4 constituting the second leg L2 are set with a dead time to prevent arm short-circuiting. Similarly, the switching elements Q5 and Q7 constituting the third leg L3 of the second full-bridge circuit 12 and the switching elements Q6 and Q8 constituting the fourth leg L4 are set with a dead time to prevent arm short-circuiting. In the first leg L1, the dead time is set as a period during which the switching elements Q1 and Q3 are simultaneously turned off. By providing this period, arm short-circuiting that occurs when the switching elements Q1 and Q3 are simultaneously turned on can be prevented. The same applies to the other legs.

[0043] In the power conversion device 1 according to this embodiment, when biased magnetization occurs in the transformer TR, the biased magnetization is suppressed by adjusting the dead time of each switching element related to the step-up switching and the step-down switching on a leg-by-leg basis. Specifically, the length of the dead time is increased or decreased on a leg-by-leg basis so that the DC component included in the excitation current Itr2 of the transformer TR is reduced, thereby controlling the voltage applied to the excitation inductance Lm.

[0044] The suppression of bias magnetization due to the length of the dead time will be explained using Figures 6 and 7. Figure 6 illustrates the flow of current Itr1 when the dead time provided to switching elements Q2 and Q4 is relatively short (the dead time period is short). Figure 6(a) illustrates the current path of current Itr1 with dashed arrows, and Figure 6(b) illustrates a graph showing the transition of current Itr1. Note that Figure 6(a) omits the first input / output terminal pair 13 (input / output terminals 13p, 13m) and second input / output terminal pair 14 (input / output terminals 14p, 14m) shown in Figure 5. The vertical axis of Figure 6(b) represents the magnitude of the current, and the horizontal axis represents the passage of time. The solid-line circle in Figure 6(b) represents the timing when current Itr1 transitions from the positive side to the negative side and becomes zero.

[0045] As shown in Figure 6(b), when the dead time period provided for switching elements Q2 and Q4 is relatively short, switching element Q2 turns on before current Itr1, which transitions from positive to negative, reaches zero, and current Itr1 follows the current path indicated by the thick dashed-dotted arrow in Figure 6(a). That is, the current path of current Itr1 is the transformer TR (primary side) → first reactance Lr1 → impedance RL → node p1 → switching element Q3 → input voltage Vi → switching element Q2 → node p2 → transformer TR (primary side). Therefore, current Itr1 transitions continuously from positive to negative, as shown in Figure 6(b).

[0046] FIG. 7 illustrates the flow of current Itr1 when the dead time provided for switching elements Q2 and Q4 is relatively long (the dead time period is long). In FIG. 7(a), the current path of current Itr1 is illustrated by dashed arrows, and FIG. 7(b) illustrates a graph showing the transition of current Itr1. In FIG. 7(a), the first input / output terminal pair 13 (input / output terminals 13p, 13m) and the second input / output terminal pair 14 (input / output terminals 14p, 14m) shown in FIG. 5 are omitted. In FIG. 7(b), the vertical axis represents the magnitude of the current, and the horizontal axis represents the passage of time. In FIG. 7(b), the areas indicated by dashed-dotted circled areas z1 to z3 represent the period during which current Itr1 maintains a zero value (a discontinuous current period during which no current flows) as it transitions from the positive side to the negative side.

[0047] As shown in FIGS. 7(a) and 7(b), when the dead time periods provided for the switching elements Q2 and Q4 are relatively long, the switching element Q2 is turned on. When the current Itr1, which flows from the positive side to the negative side, reaches zero (solid line circle in Figure 7(b)), a current discontinuity period (z1 to z3 in Figure 7(b)), during which no current flows and remains at zero until the dead time period has elapsed, is created. However, during this current discontinuity period, minute currents flow as excitation currents and currents caused by parasitic components of the devices (transformer TR and switching elements Q1 to Q4) (these currents are ignored in Figure 7(b)). This current path, as shown by the dashed arrow in Figure 7(a), is the transformer TR (primary side) → first reactance Lr1 → impedance RL → connection point p1 → diode D1 → input voltage Vi → diode D4 → connection point p2 → transformer TR (primary side). In this embodiment, this includes a state in which a minute current caused by a parasitic component of the device (a current caused by a parasitic component of the device or an excitation current) flows, and is called a current discontinuous period.

[0048] Comparing the current path indicated by the dashed arrow in Figure 7(a) with the current path indicated by the dashed arrow in Figure 6(a), it can be seen that the polarity of the voltage applied to the magnetizing inductance Lm is reversed. That is, in Figure 6(a), one end of the magnetizing inductance Lm connected to the first reactance Lr1 is connected to the negative side of the input voltage Vi, and the other end is connected to the positive side of the input voltage Vi. On the other hand, in Figure 7(a), one end of the magnetizing inductance Lm connected to the first reactance Lr1 is connected to the positive side of the input voltage Vi, and the other end is connected to the negative side of the input voltage Vi.

[0049] In this embodiment, when biased magnetism (DC component of excitation current) occurs, the dead time period of each switching element related to the voltage step-up operation and voltage step-down operation is varied on a leg-by-leg basis, thereby applying a voltage in a direction that reduces the DC component of the excitation current Itr2 flowing through the excitation inductance Lm, thereby suppressing the biased magnetism occurring in the transformer TR.

[0050] (Output fluctuations when switching between boost and buck) In the power conversion device 1, which is the premise of this embodiment, for example, it is possible to switch between step-up operation and step-down operation by relatively changing the phase shift amounts related to the ON / OFF of each switching element included in the first leg L1 to the fourth leg L4. For example, when switching the operation of the DC / DC converter 10 from step-down operation to step-up operation with the first input / output terminal pair 13 side as the primary side and the second input / output terminal pair 14 side as the secondary side, the phase shift amount of the second leg L2 relative to the first leg L1 is reduced to 0. Then, while maintaining the phase shift amount of the second leg L2 relative to the first leg L1 at 0, the phase shift amount of the fourth leg L4 relative to the second leg L2 is adjusted from 0 to a desired phase value. Here, the phase shift amount of the second leg L2 relative to the first leg L1 can be expressed as the delay (TΦ) between the falling edge when the switching element Q3 changes from ON to OFF and the falling edge when the switching element Q4 changes from ON to OFF. The phase shift of the fourth leg L4 relative to the second leg L2 can be expressed as the delay (TΦ) between the falling edge when switching element Q4 changes from ON to OFF and the falling edge when switching element Q8 changes from ON to OFF. Note that because the ON / OFF states of switching elements Qn (n=1 to 8) change at a predetermined cycle (T), the delay (TΦ) can also be expressed as a phase lead (TΦ).

[0051] Furthermore, for example, when switching the operation of DC / DC converter 10 from step-up operation to step-down operation with first input / output terminal pair 13 as the primary side and second input / output terminal pair 14 as the secondary side, the phase shift amount of fourth leg L4 relative to second leg L2 is reduced to 0. Then, while keeping the phase shift amount of fourth leg L4 relative to second leg L2 at 0, the phase shift amount of first leg L1 relative to second leg L2 is adjusted from 0 to a desired phase value. In this way, in power conversion device 1, step-up and step-down operations are continuously switched by relatively changing the phase shift amounts related to the ON / OFF of each switching element included in first leg L1 to fourth leg L4.

[0052] In the following description, the terms "step-up operation" and "step-down operation" of the DC / DC converter 10 refer to the operation based on the switching patterns related to the ON / OFF of each switching element included in the first leg L1 to the fourth leg L4, and do not refer to the relationship between the input voltage and the output voltage related to voltage conversion. In other words, in this embodiment, the DC / DC converter 10 may operate with the input voltage greater than the output voltage during "step-up operation," and may also operate with the input voltage less than the output voltage during "step-down operation." The step-up operation of the DC / DC converter 10 is also referred to as the "step-up mode," and the step-down operation is also referred to as the "step-down mode." Switching from the step-up mode to the step-down mode will be described assuming that the phase shift from the step-up mode is minimum TΦ (the phase shift from the step-down mode is maximum TΦ). The step-up mode with the minimum phase shift TΦ is also referred to as the "step-up mode minimum TΦ," and the step-down mode with the maximum phase shift TΦ is also referred to as the "step-down mode maximum TΦ."

[0053] In the DC / DC converter 10 of the power conversion device 1 that is the premise of this embodiment, the current path in the step-up mode is different from the current path in the step-down mode, and the current waveform flowing through the transformer TR is also different. For this reason, for example, when the operation mode is switched from step-up mode minimum TΦ to step-down mode maximum TΦ, an output difference occurs. Below, with reference to Figures 8 to 13, the output fluctuation of the DC / DC converter 10 when switching between step-up and step-down modes will be described.

[0054] First, the output difference occurring on the positive side of the transformer current will be explained using Figures 8 to 10. Figure 8 is a diagram illustrating the current path in boost mode. Figure 8(a) shows the current path with solid arrows when switching elements Q1 and Q4 of first full-bridge circuit 11 are ON and switching element Q8 of second full-bridge circuit 12 is ON, and Figure 8(b) shows the current path during the dead time after switching shown in Figure 8(a) with solid arrows.

[0055] 8(a), in the first full-bridge circuit 11, a current flows through the following current path: input voltage Vi (positive side) → switching element Q1 → connection point p1 → impedance RL → first reactor Lr1 → excitation inductance Lm → connection point p2 → switching element Q4 → input voltage Vi (negative side). Similarly, in the second full-bridge circuit 12, a current flows through the following current path: transformer TR (secondary side) → second reactor Lr2 → connection point p3 → diode D5 → output voltage Vo → switching element Q8 → connection point p4 → transformer TR (secondary side).

[0056] During the dead time, as shown by the solid arrows in FIG. 8(b), in the first full-bridge circuit 11, a current flows through the following current path: input voltage Vi (negative side) → diode D3 → connection point p1 → impedance RL → first reactor Lr1 → excitation inductance Lm → connection point p2 → diode D2 → input voltage Vi (positive side). This current is caused by, for example, energy stored in the excitation inductance Lm of the transformer TR, the first reactor Lr1, and the parasitic capacitance of the device. Similarly, in the second full-bridge circuit 12, a current flows through the following current path: transformer TR (secondary side) → second reactor Lr2 → connection point p3 → diode D5 → output voltage Vo → diode D8 → connection point p4 → transformer TR (secondary side).

[0057] FIG. 9 is a diagram illustrating the current paths when TΦ is minimum in boost mode and TΦ is maximum in buck mode. FIG. 9(a) shows the current path when TΦ is minimum in boost mode, and FIG. 9(b) shows the current path when TΦ is maximum in buck mode. In FIGS. 9(a) and 9(b), the current paths are indicated by solid arrows. Note that the current path when TΦ is minimum in boost mode and the current path when TΦ is maximum in buck mode are current paths formed in a transition state after the dead time shown in FIG. 8(b).

[0058] In the boost mode with minimum TΦ, as shown in FIG. 9(a), the first full-bridge circuit In this state, switching elements Q2 and Q3 of first full-bridge circuit 11 are turned ON, and switching element Q7 of second full-bridge circuit 12 is turned ON. As shown by the solid arrows, in first full-bridge circuit 11, current flows through the following current path: input voltage Vi (negative side) → switching element Q3 → connection point p1 → impedance RL → first reactor Lr1 → excitation inductance Lm → connection point p2 → switching element Q2 → input voltage Vi (positive side). In the second full-bridge circuit 12, current flows through the following current path: transformer TR (secondary side) → second reactor Lr2 → connection point p3 → switching element Q7 → diode D8 → connection point p4 → transformer TR (secondary side).

[0059] Furthermore, in the step-down mode at maximum TΦ, as shown in FIG. 9(b), the switching elements Q2 and Q3 of the first full-bridge circuit 11 are turned on, and the switching element Qn (n=5 to 8) of the second full-bridge circuit 12 is controlled to be off. Therefore, in the first full-bridge circuit 11 in the step-down mode at maximum TΦ, a current flows through the same current path as in the step-up mode at minimum TΦ shown in FIG. 9(a). However, in the second full-bridge circuit 12 in the step-down mode at maximum TΦ, because the switching elements Qn (n=5 to 8) are controlled to be off, a current flows through the following current path: transformer TR (secondary side) → second reactor Lr2 → connection point p3 → diode D5 → output voltage Vo → diode D8 → connection point p4 → transformer TR (secondary side).

[0060] 9(a) and 9(b), the current paths on the first full-bridge circuit 11 side are similar, but the current paths on the second bridge circuit 12 side are different between the step-up mode minimum TΦ and the step-down mode maximum TΦ. Therefore, when the operation mode is switched from the step-up mode minimum TΦ to the step-down mode maximum TΦ, an output difference occurs in the current flowing through the transformer TR.

[0061] Figure 10 is a graph showing the transition of current at minimum TΦ in boost mode and maximum TΦ in buck mode. The vertical axis represents the magnitude of current (A), and the horizontal axis represents the passage of time (μs). In Figure 10, the dashed line graph represents the transition of current flowing through the transformer TR at minimum TΦ in boost mode, and the solid line graph represents the transition of current flowing through the transformer TR at maximum TΦ in buck mode. As shown in the area surrounded by the solid ellipse z4, an output difference occurs in the current flowing through the transformer TR, with maximum TΦ in buck mode being greater than minimum TΦ in boost mode. The positive peak value of the current at minimum TΦ in boost mode is smaller than that at maximum TΦ in buck mode, and the slope of the decrease from the peak value to zero is also gentler than that at maximum TΦ in buck mode.

[0062] Next, the output difference occurring on the negative side of the transformer current will be explained. Fig. 11 is a diagram illustrating the current path in boost mode. Fig. 11(a) shows the current path with solid arrows when switching elements Q2 and Q3 of first full-bridge circuit 11 are ON and switching element Q7 of second full-bridge circuit 12 is ON, and Fig. 11(b) shows the current path during the dead time after switching shown in Fig. 11(a) with solid arrows.

[0063] 11(a), in the first full-bridge circuit 11, a current flows through the following current path: input voltage Vi (positive side) → switching element Q2 → connection point p2 → excitation inductance Lm → first reactor Lr1 → impedance RL → connection point p1 → switching element Q3 → input voltage Vi (negative side). Similarly, in the second full-bridge circuit 12, a current flows through the following current path: transformer TR (secondary side) → connection point p4 → diode D6 → output voltage Vo → switching element Q7 → connection point p3 → second reactor Lr2 → transformer TR (secondary side).

[0064] During the dead time, as shown by the solid arrow in FIG. 11(b), In the full-bridge circuit 11, current flows through the following current path: input voltage Vi (negative side) → diode D4 → connection point p2 → excitation inductance Lm → first reactor Lr1 → impedance RL → connection point p1 → diode D1 → input voltage Vi (positive side). In FIG. 11(b), this current also originates from energy stored in the excitation inductance Lm of the transformer TR, the first reactor Lr1, and the parasitic capacitance of the device. Similarly, in the second full-bridge circuit 12, current flows through the following current path: transformer TR (secondary side) → connection point p4 → diode D6 → output voltage Vo → diode D7 → connection point p3 → second reactor Lr2 → transformer TR (secondary side).

[0065] FIG. 12 is a diagram illustrating the current paths in the boost mode at minimum TΦ and the buck mode at maximum TΦ. FIG. 12(a) shows the current path in the boost mode at minimum TΦ, and FIG. 12(b) shows the current path in the buck mode at maximum TΦ. In FIGS. 12(a) and 12(b), the current paths are indicated by solid arrows. Note that the current path in the boost mode at minimum TΦ and the current path in the buck mode at maximum TΦ are current paths formed in a transition state after the dead time shown in FIG. 11(b).

[0066] 12(a), in the boost mode at minimum TΦ, switching elements Q1 and Q4 of the first full-bridge circuit 11 are ON, and switching element Q8 of the second full-bridge circuit 12 is ON. As indicated by the solid arrows, in the first full-bridge circuit 11, current flows through the following current path: input voltage Vi (negative side) → switching element Q4 → connection point p2 → excitation inductance Lm → first reactor Lr1 → impedance RL → connection point p1 → switching element Q1 → input voltage Vi (positive side). In the second full-bridge circuit 12, current flows through the following current path: transformer TR (secondary side) → connection point p4 → switching element Q8 → diode D7 → connection point p3 → second reactor Lr2 → transformer TR (secondary side).

[0067] In the step-down mode at maximum TΦ, as shown in FIG. 12(b), the switching elements Q1 and Q4 of the first full-bridge circuit 11 are turned on, and the switching element Qn (n=5 to 8) of the second full-bridge circuit 12 is controlled to be off. Therefore, in the first full-bridge circuit 11 in the step-down mode at maximum TΦ, a current flows through the same current path as in the step-up mode at minimum TΦ shown in FIG. 12(a). However, in the second full-bridge circuit 12, because the switching elements Qn (n=5 to 8) are controlled to be off, a current flows through the following current path: transformer TR (secondary side) → connection point p4 → diode D6 → output voltage Vo → diode D7 → connection point p3 → second reactor Lr2 → transformer TR (secondary side).

[0068] 12(a) and 12(b), the current paths on the first full-bridge circuit 11 side are similar, but the current paths on the second bridge circuit 12 side are different between the step-up mode minimum TΦ and the step-down mode maximum TΦ. Therefore, when the operation mode is switched from the step-up mode minimum TΦ to the step-down mode maximum TΦ, an output difference occurs in the current flowing through the transformer TR.

[0069] FIG. 13 is a graph showing the transition of current at minimum TΦ in boost mode and maximum TΦ in buck mode. The vertical axis represents the magnitude of current (A), and the horizontal axis represents the passage of time (μs). In FIG. 13, the dashed line graph represents the transition of current flowing through the transformer TR at minimum TΦ in boost mode, and the solid line graph represents the transition of current flowing through the transformer TR at maximum TΦ in buck mode. As shown in the area surrounded by the solid ellipse z5, an output difference occurs in the current flowing through the transformer TR, with maximum TΦ in buck mode being greater than minimum TΦ in boost mode. The negative peak value of the current at minimum TΦ in boost mode is smaller than that at maximum TΦ in buck mode, and the increase slope from the peak value to zero is also gentler than that at maximum TΦ in buck mode.

[0070] 9(a) and 9(b), the difference between the boost mode minimum TΦ and the buck mode maximum TΦ is that the switching element Q7 of the third leg L3 is ON. Similarly, comparing the current paths shown in FIGS. 12(a) and 12(b), the difference between the boost mode minimum TΦ and the buck mode maximum TΦ is that the switching element Q8 of the fourth leg L4 is ON. The current paths for the boost mode minimum TΦ and the buck mode maximum TΦ shown in FIGS. 9(a) and 9(b) are due to switching after the dead time shown in FIG. 8(b), and the current paths for the boost mode minimum TΦ and the buck mode maximum TΦ shown in FIGS. 12(a) and 12(b) are due to switching after the dead time shown in FIG. 11(b).

[0071] 8(b) , the same current path as in the buck mode maximum TΦ can be formed before the switching element Q7 in the boost mode minimum TΦ is turned on. In other words, by switching from the boost mode minimum TΦ to the buck mode maximum TΦ within the extended dead time of the third leg L3, output fluctuations due to differences in the current path at the time of switching between the boost and buck modes can be suppressed. 12(a) and 12(b). For example, by relatively extending (increasing) the dead time of the fourth leg L4 shown in FIG. 11(b), the same current path as that in the buck mode maximum TΦ can be formed before the switching element Q8 in the boost mode minimum TΦ is turned on. In this case, too, by switching from the boost mode minimum TΦ to the buck mode maximum TΦ within the extended dead time of the fourth leg L4, output fluctuations due to differences in the current path at the time of switching between the boost and buck modes can be suppressed. In the power conversion device 1 according to this embodiment, the dead time of some legs related to switching is extended (increased) to ensure the same current path between the minimum TΦ of the step-up switching and the maximum TΦ of the step-down switching. However, since an increase in the dead time may increase the step-up / step-down conversion loss, the dead time of other legs is changed to the minimum period.

[0072] FIG. 14 is a graph showing the transition of current in the step-up mode and the step-down mode according to this embodiment. The vertical axis represents the magnitude of current (A), and the horizontal axis represents the passage of time (μs). In FIG. 14, the dashed line graph represents the transition of current flowing through the transformer TR in the step-up mode, and the solid line graph represents the transition of current in the step-down mode. As shown in FIG. 14, the transition of current in the step-up mode and the step-down mode show the same trend. Therefore, even when switching from the step-up mode minimum TΦ to the step-down mode maximum TΦ, no output fluctuation occurs. Furthermore, as shown in the regions of the solid-line circles z6 and z7, in the regions where the current flowing through the transformer TR transitions from the positive side to the negative side and from the negative side to the positive side, a certain period (current discontinuity period) during which the current value remains zero is ensured. By extending (increasing) the dead time for some legs related to switching, the DC component of the excitation current flowing through the transformer TR can be suppressed.

[0073] Fig. 15 is a graph illustrating the transition of the phase shift amount during voltage step-up / step-down switching in this embodiment. The vertical axis of Fig. 15 represents the magnitude of output power (W), and the horizontal axis represents the phase shift amount (μs). The graph indicated by the dashed line represents the transition of the output due to the phase shift amount in the power conversion device 1 based on the assumptions described using Figs. 8 to 13, and the graph indicated by the solid line represents the transition of the output due to the phase shift amount in the power conversion device 1 of this embodiment.

[0074] As shown in Fig. 15, the DC / DC converter 10 switches from the step-up mode to the step-down mode at a phase shift of 13 µs. This phase shift corresponds to the minimum TΦ in the step-up mode and the maximum TΦ in the step-down mode. In the power conversion device 1 used as the premise, as shown by the solid line, an output difference of about 200 W occurs when switching from the minimum TΦ in the step-up mode to the maximum TΦ in the step-down mode. In contrast, in the power conversion device 1 of this embodiment, As shown by the dashed line, switching from the minimum TΦ of the voltage step-up mode to the maximum TΦ of the voltage step-down mode is performed without generating an output difference. According to this embodiment, it is possible to more efficiently and quickly switch between voltage step-up and voltage step-down operation modes while suppressing output fluctuations of the power conversion device 1.

[0075] <Processing flow> Next, switching control of the power conversion device 1 according to this embodiment will be described with reference to Fig. 16 and Fig. 17. The control unit 20 of the power conversion device 1 according to this embodiment generates control signals Gn (n = 1 to 8) based on voltage values ​​measured by, for example, a voltage sensor 15p provided in the first input / output terminal pair 13 of the DC / DC converter 10 and a voltage sensor 15s provided in the second input / output terminal pair 14, and outputs the control signals to the gate terminals of the corresponding switching elements Qn (n = 1 to 8). However, the control unit 20 of the power conversion device 1 may also generate the control signals Gn (n = 1 to 8) using measurement values ​​(current values) of various sensors provided in the DC / DC converter 10 for measuring the magnitude of input / output currents.

[0076] (Boost switching) Fig. 16 is a timing chart showing transitions in the control state during boost switching. In Fig. 16(a), a graph showing transitions in the transformer current IL (current flowing through the first reactor Lr1) flowing through the transformer TR is represented by a dashed line. The vertical axis in Fig. 16(a) represents the relative magnitude of the transformer current IL, and the horizontal axis represents the passage of time. As shown in the dashed line graph in Fig. 16(a), in the DC / DC converter 10 according to this embodiment, there are current discontinuity periods during which the current flowing through the transformer TR remains zero in the periods t1-t2, t5-t6, and t9-t10.

[0077] 16(b) through 16(e) show the transitions of the ON and OFF periods of each switching element constituting the first through fourth legs L1 through L4, respectively. Specifically, in FIG. 16(b), the transitions of the ON and OFF periods of switching element Q1 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q3 are shown by dashed lines. In FIG. 16(c), the transitions of the ON and OFF periods of switching element Q2 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q4 are shown by dashed lines. Similarly, in FIG. 16(d), the transitions of the ON and OFF periods of switching element Q5 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q7 are shown by dashed lines. In FIG. 16(e), the transitions of the ON and OFF periods of switching element Q6 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q8 are shown by dashed lines. In Figures 16(b) to 16(e), the vertical axis represents the ON / OFF state of each switching element, and the vertical axis represents the passage of time. Note that "1" on the vertical axis in Figures 16(b) to 16(e) represents the ON state of each switching element (drain terminal and source terminal are conductive), and "0" represents the OFF state of each switching element (drain terminal and source terminal are open).

[0078] In the power conversion device 1 according to this embodiment, during boost switching, the length of the dead time (simultaneous OFF) period for each of the switching elements constituting the first leg L1 to the fourth leg L4 is adjusted as follows. The length of the period during which the switching elements Q2 and Q4 of the second leg L2 are simultaneously turned off is relatively increased. The length of the simultaneous OFF period of the other legs (for example, the first leg L1) is made relatively short. The length of the simultaneous OFF period of the third leg L3 and the fourth leg L4 is not fixed, but is variable. The switching element Q5 of the third leg L3 and the switching element Q6 of the fourth leg L4 may be always turned off (no synchronous rectification).

[0079] As already explained, in the power conversion device 1 including the DC / DC converter 10, a period during which the switching elements constituting the first leg L1 to the fourth leg L4 are simultaneously turned off is uniformly set as dead time to prevent arm short-circuiting of the switching elements. The period of such dead time is set with a certain degree of variable width in consideration of the specifications and required performance of the power conversion device 1, the switching delay of each switching element constituting the DC / DC converter 10, the characteristics of various devices, etc. The minimum value of this variable width is set as the minimum dead time period (Tds), and the maximum value is set as the maximum dead time period (Tdl). Generally, the longer the dead time (simultaneous OFF period), the greater the loss in power conversion during voltage step-up / step-down. Therefore, it is desirable to set the dead time to be short.

[0080] In the power conversion device 1 according to this embodiment, the dead time of the transformer current IL flowing through the transformer TR is controlled to be long only during the period when the current is discontinuous (zero current value section), thereby suppressing the bias magnetism occurring in the transformer TR while suppressing the relative loss reduction.

[0081] The current discontinuity periods of t5-t6 and t9-t10 in FIG. 16(a) are taken as examples. As shown in FIG. 16(c), in the power conversion device 1 according to this embodiment, the length of the period (dead time) during which the switching elements Q2 and Q4 of the second leg L2 are simultaneously OFF is set as the maximum dead time period (Tdl). As shown in FIG. 16(b), the length of the period (dead time) during which the switching elements Q1 and Q3 of the first leg L1 are simultaneously OFF is set as the minimum dead time period (Tds). As a result, as shown in FIGS. 16(b) and 16(c), the dead time of the second leg L2 is relatively large (longer) than the dead time of the first leg L1 because the difference (maximum dead time period (Tdl) - minimum dead time period (Tds)) is extended.

[0082] For example, in the t9-t10 interval, comparing the ON period of switching element Q1 shown by the solid line in Fig. 16(b) with the ON period of switching element Q4 shown by the dashed line in Fig. 16(c), it is clear that the period indicated by the dotted hatched area is added to the rising edge of the ON period of switching element Q1, making the ON period of switching element Q1 relatively longer. Similarly, in the t5-t6 interval, comparing the ON period of switching element Q3 shown by the dashed line in Fig. 16(b) with the ON period of switching element Q2 shown by the solid line in Fig. 16(c), it is clear that the period indicated by the diagonally hatched area is added to the rising edge of the ON period of switching element Q3, making the ON period of switching element Q3 relatively longer.

[0083] In the third leg L3, for example, as shown in the section t3-t6 of FIG. 16(d), the rising edge of the ON period of switching element Q5 is set to be the minimum dead time (Tds) relative to the falling edge of the ON period of switching element Q7. The rising edge of the ON period of switching element Q7 is varied in accordance with the phase shift amount (TΦ) so that it is at least the maximum dead time (Tdl) relative to the falling edge of the ON period of switching element Q5. The phase shift amount (TΦ) is expressed, for example, as the difference between the falling edge of the ON period of switching element Q2 constituting the second leg L2 and the falling edge of the ON period of switching element Q7. As shown in the rising edge of the ON period of switching element Q5 at t4 of FIG. 16(d), the period indicated by the hatched area is added, and the ON period of the switching element is extended.

[0084] Furthermore, in the fourth leg L4, for example, as shown in the section t7-t10 of FIG. 16(e), the rising edge of the ON period of the switching element Q6 is set to be the minimum dead time period (Tds) relative to the falling edge of the ON period of the switching element Q8. The phase shift amount (TΦ) is varied according to the phase shift amount (TΦ) so that the dead time is at least equal to or greater than the maximum dead time period (Tdl) relative to the falling edge of the ON period of switching element Q4 constituting the second leg L2. Here, the phase shift amount (TΦ) is expressed, for example, as the difference between the falling edge of the ON period of switching element Q4 and the falling edge of the ON period of switching element Q8 constituting the second leg L2. As shown in FIG. 16(e) at t8 in the rising edge of the ON period of switching element Q6, the period indicated by the hatched area is added, and the ON period of that switching element is extended.

[0085] (Step-down switching) Fig. 17 is a timing chart showing transitions in the control state during step-down switching. In Fig. 17(a), a graph showing transitions in the transformer current IL (current flowing through the first reactor Lr1) flowing through the transformer TR is represented by a dashed line. The vertical axis in Fig. 17(a) represents the relative magnitude of the transformer current IL, and the horizontal axis represents the passage of time. As shown in the dashed line graph in Fig. 17(a), in the DC / DC converter 10 according to this embodiment, there are current discontinuity periods during which the current flowing through the transformer TR remains zero in sections t1-t2, t5-t6, and t9-t10.

[0086] 17(b) through 17(e) show the transitions of the ON and OFF periods of each switching element constituting the first through fourth legs L1 through L4, respectively. Specifically, in FIG. 17(b), the transitions of the ON and OFF periods of switching element Q1 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q3 are shown by dashed lines. In FIG. 17(c), the transitions of the ON and OFF periods of switching element Q2 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q4 are shown by dashed lines. Similarly, in FIG. 17(d), the transitions of the ON and OFF periods of switching element Q5 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q7 are shown by dashed lines. In FIG. 17(e), the transitions of the ON and OFF periods of switching element Q6 are shown by solid lines, and the transitions of the ON and OFF periods of switching element Q8 are shown by dashed lines. In Figures 17(b) to 17(e), the vertical axis represents the ON / OFF state of each switching element, and the vertical axis represents the passage of time. A "1" on the vertical axis in Figures 17(b) to 17(e) represents that each switching element is ON (the drain terminal and source terminal are conductive), and a "0" represents that each switching element is OFF (the drain terminal and source terminal are open).

[0087] In the power conversion device 1 according to this embodiment, during step-down switching, the length of the dead time (simultaneous OFF) period for each of the switching elements constituting the first leg L1 to the fourth leg L4 is adjusted as follows. The length of the period during which the switching elements Q1 and Q3 of the first leg L1 are simultaneously turned off is relatively reduced. The length of the simultaneous OFF period of the other legs (for example, the second leg L2) is made relatively long. The length of the simultaneous OFF period of the third leg L3 and the fourth leg L4 is not fixed, but is variable. The switching elements Q5 and Q7 of the third leg L3 and the switching elements Q6 and Q8 of the fourth leg L4 may be always OFF (no synchronous rectification).

[0088] In the power conversion device 1 according to this embodiment, in the step-down switching, as in the step-up switching, the dead time is controlled to be long only during the period when the transformer current IL flowing through the transformer TR is discontinuous (zero current value section), thereby suppressing the relative loss reduction while suppressing the bias magnetism occurring in the transformer TR.

[0089] As shown in FIG. 17(b), in the step-down switching, in the power conversion device 1 according to this embodiment, there is a period ( The length of the period during which the switching elements Q2 and Q4 of the second leg L2 are simultaneously turned off is set as the minimum dead time period (Tds). Then, as shown in FIG. 17(c), the length of the period during which the switching elements Q2 and Q4 of the second leg L2 are simultaneously turned off is set as the maximum dead time period (Tdl). As a result, the length of the dead time of the second leg L2 in the t5-t6 and t9-t10 sections is relatively large (longer) than the dead time set in the first leg L1, i.e., the difference between the maximum dead time period (Tdl) and the minimum dead time period (Tds).

[0090] In the t3-t5 period in Figure 17(b), the period indicated by the hatched area is added to the rising edge of the ON period of switching element Q3 indicated by the dashed line, and it can be seen that the dead time between the rising edge and the falling edge of the ON period of switching element Q1 indicated by the solid line is shortened. Similarly, in the t7-t9 period, the period indicated by the hatched area is added to the rising edge and the falling edge of the ON period of switching element Q1 indicated by the solid line, and it can be seen that the dead time between the falling edge and the falling edge of the ON period of switching element Q3 indicated by the dashed line is shortened. The phase shift amount (TΦ) in the step-down switching is expressed as the difference between the falling edge of the ON period of switching element Q4 in the second leg L2 and the falling edge of the ON period of switching element Q3 in the first leg L1.

[0091] 17(d), for example, the falling edge of the ON period of switching element Q5 is varied in accordance with the phase shift amount (TΦ) so as to be at least the maximum dead time period (Tdl) relative to the rising edge of the ON period of switching element Q7. Also, in the t9-t10 period, the rising edge of the ON period of switching element Q5 is varied in accordance with the phase shift amount (TΦ) so as to be at least the maximum dead time period (Tdl) relative to the falling edge of the ON period of switching element Q7.

[0092] 17(e), the rising edge of the ON period of switching element Q6 is varied in accordance with the phase shift amount (TΦ) so as to be at least the maximum dead time period (Tdl) relative to the falling edge of the ON period of switching element Q8. Then, as shown in the t9-t10 section, the rising edge of the ON period of switching element Q8 is varied in accordance with the phase shift amount (TΦ) so as to be at least the maximum dead time period (Tdl) relative to the falling edge of the ON period of switching element Q6.

[0093] (Variation) In the embodiment, the description has been given of step-up switching and step-down switching in which the first full-bridge circuit 11 connected to the first input / output terminal pair 13 of the power conversion device 1 serves as the primary side. The same applies to step-up switching and step-down switching in which the second full-bridge circuit 12 connected to the second input / output terminal pair 13 of the power conversion device 1 serves as the primary side. The control unit 20 of the power conversion device 1 may determine which side of the first full-bridge circuit 11 or the second full-bridge circuit 12 serves as the secondary side by determining the power running / regenerative operating state.

[0094] (others) The above-described embodiment is merely an example, and the disclosure of the present embodiment may be modified as appropriate within the scope of the gist thereof. The processes and means described in the present disclosure may be freely combined and implemented as long as no technical contradictions arise. For example, in the examples, the DC / DC converter 10 of the power conversion device 1 is described as an isolated bidirectional DC / DC converter, but the processes and means described in the present disclosure can also be applied to an isolated bidirectional buck-boost chopper or a bidirectional multifunction chopper.

[0095] Furthermore, a process described as being performed by one circuit or device may be shared and performed by multiple circuits or devices, or a process described as being performed by different circuits or devices may be performed by a single circuit or device.

[0096] In the following, the constituent elements of the present disclosure will be described with the reference numerals in the drawings so that the constituent elements of the present disclosure can be compared with the configurations of the examples. <Appendix 1> a DC / DC converter (10) including: a first full-bridge circuit (11) including a first switching leg (L1) and a second switching leg (L2) connected in parallel to a first input / output terminal pair (13); a second full-bridge circuit (12) including a third switching leg (L3) and a fourth switching leg (L4) connected in parallel to a second input / output terminal pair (14); and a transformer (TR) including one winding (Wn1) connected to the first full-bridge circuit (11) and the other winding (Wn2) connected to the second full-bridge circuit (12); a control unit (20) that controls the DC / DC converter (10), the first switching leg (L1) has a first switching element (Q1) and a third switching element (Q3), a source terminal of the first switching element (Q1) and a drain terminal of the third switching element (Q3) are connected in series at a first connection point (p1), and a drain terminal of the first switching element (Q1) and a source terminal of the third switching element (Q3) are connected to the first input / output terminal pair (13); the second switching leg (L2) has a second switching element (Q2) and a fourth switching element (Q4), a source terminal of the second switching element (Q2) and a drain terminal of the fourth switching element (Q4) are connected in series at a second connection point (p2), and a drain terminal of the second switching element (Q2) and a source terminal of the fourth switching element (Q4) are connected to the first input / output terminal pair (13); the third switching leg (L3) has a fifth switching element (Q5) and a seventh switching element (Q7), a source terminal of the fifth switching element (Q5) and a drain terminal of the seventh switching element (Q7) are connected in series at a third connection point (p3), and a drain terminal of the fifth switching element (Q5) and a source terminal of the seventh switching element (Q7) are connected to the second input / output terminal pair (14); the fourth switching leg (L4) has a sixth switching element (Q6) and an eighth switching element (Q8), a source terminal of the sixth switching element (Q6) and a drain terminal of the eighth switching element (Q8) are connected in series at a fourth connection point (p4), and a drain terminal of the sixth switching element (Q6) and a source terminal of the eighth switching element (Q8) are connected to the second input / output terminal pair (14); one winding (Wn1) of the transformer (TR) is connected to a first connection point (p1) of the first switching leg (L1) and a second connection point (p2) of the second switching leg (L2), and the other winding (Wn2) of the transformer (TR) is connected to a third connection point (p3) of the third switching leg (L3) and a fourth connection point (p4) of the fourth switching leg (L4); The control unit (20) When a boost operation is performed, a first reference control signal is output to the first switching element (Q1) and the third switching element (Q3) of the first full bridge circuit (11), the first reference control signal turning the first switching element (Q1) on or off; a first reference inverted signal obtained by inverting the phase of the first reference control signal is output to the second switching element (Q2) and the fourth switching element (Q2); extend a period during which at least the second switching element (Q2) and the fourth switching element (Q4) of the second switching leg (L2) are simultaneously turned off, and make it longer than a period during which the first switching element (Q1) and the third switching element (Q3) of the first switching leg (L1) are simultaneously turned off; A power conversion device (1) characterized by: [Explanation of symbols]

[0097] 1 Power conversion device 10 DC / DC converter 11 First full-bridge circuit 12 Second full-bridge circuit 13 First input / output terminal pair 14 Second input / output terminal pair 20 Control Unit L1 First switching leg L2 Second switching leg L3 Third switching leg L4 Fourth switching leg Lr1 First reactor Lr2 Second reactor Lm Excitation inductance p1 First connection point p2 Second connection point p3 Third connection point p4 4th connection point Q1 First switching element Q2 Second switching element Q3 Third switching element Q4 Fourth switching element Q5 Fifth switching element Q6 6th switching element Q7 Seventh switching element Q8 8th switching element TR transformer Wn1 First winding Wn2 Second winding

Claims

1. a DC / DC converter including: a first full bridge circuit including a first switching leg and a second switching leg connected in parallel to a first input / output terminal pair; a second full bridge circuit including a third switching leg and a fourth switching leg connected in parallel to a second input / output terminal pair; and a transformer including one winding connected to the first full bridge circuit and the other winding connected to the second full bridge circuit; a control unit that controls the DC / DC converter, the first switching leg has a first switching element and a third switching element, a source terminal of the first switching element and a drain terminal of the third switching element are connected in series at a first connection point, and a drain terminal of the first switching element and a source terminal of the third switching element are connected to the first input / output terminal pair; the second switching leg has a second switching element and a fourth switching element, a source terminal of the second switching element and a drain terminal of the fourth switching element are connected in series at a second connection point, and a drain terminal of the second switching element and a source terminal of the fourth switching element are connected to the first input / output terminal pair; the third switching leg has a fifth switching element and a seventh switching element, a source terminal of the fifth switching element and a drain terminal of the seventh switching element are connected in series at a third connection point, and a drain terminal of the fifth switching element and a source terminal of the seventh switching element are connected to the second input / output terminal pair; the fourth switching leg has a sixth switching element and an eighth switching element, a source terminal of the sixth switching element and a drain terminal of the eighth switching element are connected in series at a fourth connection point, and a drain terminal of the sixth switching element and a source terminal of the eighth switching element are connected to the second input / output terminal pair; one winding of the transformer is connected to a first connection point of the first switching leg and a second connection point of the second switching leg, and the other winding of the transformer is connected to a third connection point of the third switching leg and a fourth connection point of the fourth switching leg; The control unit When a boost operation is performed, a first reference control signal is output to the first switching element and the third switching element of the first full bridge circuit, for turning the first switching element ON or OFF; a first reference inverted signal obtained by inverting the phase of the first reference control signal is output to the second switching element and the fourth switching element; extending a period during which at least the second switching element and the fourth switching element of the second switching leg are simultaneously turned off, so that the period is longer than a period during which the first switching element and the third switching element of the first switching leg are simultaneously turned off; A power conversion device characterized by:

2. When the control unit defines a delay amount from when the second switching element falls from ON to OFF until when the seventh switching element of the third switching leg falls from ON to OFF as a first phase shift amount, 2. The power conversion device according to claim 1, wherein a period during which the fifth switching element and the seventh switching element of the third switching leg are simultaneously turned off is varied according to the first phase shift amount.

3. When the control unit determines a delay amount from when the fourth switching element falls from ON to OFF until when the eighth switching element of the fourth switching leg falls from ON to OFF as a second phase shift amount, The sixth switching element and the eighth switching element of the fourth switching leg are simultaneously 3. The power conversion device according to claim 1, wherein the period during which the power supply is turned off is variable depending on the second phase shift amount.

4. The control unit When a step-down operation is performed, a control signal for turning on or off the fourth switching element of the first full bridge circuit is defined as a second reference control signal, and a delay amount from when the fourth switching element falls from on to off until the third switching element of the first switching leg falls from on to off is defined as a third phase shift amount: outputting the second reference control signal to the fourth switching element of the first full-bridge circuit, and outputting a second reference inverted signal obtained by inverting the phase of the second reference control signal to the second switching element; a third reference control signal delayed by the third phase shift amount from the second reference control signal is output to the third switching element of the first full bridge circuit, and a third reference inverted signal obtained by inverting the phase of the third reference control signal is output to the first switching element; 4. The power conversion device according to claim 1, wherein a period during which at least the first switching element and the third switching element of the first switching leg are simultaneously turned off is made shorter than a period during which the second switching element and the fourth switching element of the second switching leg are simultaneously turned off.

5. 5. The power conversion device according to claim 4, wherein the control unit varies a period during which the fifth switching element and the seventh switching element of the third switching leg are simultaneously turned off in accordance with the third phase shift amount.

6. 6. The power conversion device according to claim 4, wherein the control unit varies a period during which the sixth switching element and the eighth switching element of the fourth switching leg are simultaneously turned off in accordance with the third phase shift amount.

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