Power transfer system, integrated power device, and radio frequency method

Abstract

This article provides systems and methods for transmitting electricity.

Description

[Technical Field]

[0001] This invention relates to power transmitters, receivers, and systems and methods for power transmission. [Previous Technology]

[0002] In inductive power transmission (IPT), electricity is typically transmitted between coils via a magnetic field. Alternating current (AC) drives a transmitter coil to generate an oscillating magnetic field. The magnetic field passes through a receiver coil, where it induces AC. The induced AC can directly drive a load or be rectified to direct current (DC), which is then applied to drive the load. For high efficiency, the transmitter and receiver coils must be close together. It is common for the transmitter and receiver coils to be separated only by a portion of the coil diameter (e.g., within centimeters) and for the coil axes to be closely aligned.

[0003] In some IPT systems, resonant inductive coupling is employed. Resonant inductive coupling increases efficiency in IPT by using resonant circuits. Compared to non-resonant inductive coupling, resonant inductive coupling achieves higher efficiency over greater distances. In resonant inductive coupling, electricity is transmitted via a magnetic field between two resonant circuits (one in the transmitter and one in the receiver). The two circuits are tuned to resonate at the same resonant frequency.

[0004] In some IPT systems, the magnetic field can generate eddy currents in nearby metals. This can cause a significant temperature rise and a fire hazard. Ferrite plates can be used to provide shielding and improve inductive coupling, but this increases the cost of such systems.

[0005] Capacitive power transfer (CPT) uses an electric field to transfer power between two electrodes (such as metal plates). Typically, four metal plates are used in a CPT system to form a capacitive coupler. Two plates act as a power transmitter, and the other two act as power receivers, resulting in at least two coupling capacitors providing a power flow loop. An alternating current voltage is applied to the transmitter plates via the transmitter. An oscillating electric field induces an alternating potential on the receiver plates, causing an alternating current to flow in the load circuit. Resonance can also be used with capacitive coupling to extend the range of power transfer.

[0006] In a CPT system, eddy current losses can be reduced, and the board system used is low-cost, thus reducing system costs. However, one of the problems with many systems is that high voltages can be applied to the board. Such high voltages can generate strong electric fields, which leads to significant field emission into the surrounding area.

[0007] There are also issues related to the capacitor or inductor compensation networks in CPT and IPT systems. Currently, both CPT and IPT systems require minimal separation between the receiver and transmitter. This typically requires large capacitors and inductors in the compensation networks on both the primary and secondary sides. These large components are difficult to manufacture, and their parasitic resistance can significantly reduce system efficiency. Furthermore, these compensation components are not directly involved in the power transmission process.

[0008] Wireless power transmitters and receivers with fewer components and / or reduced costs are still desirable. Wireless power transmitters and receivers with reduced dependence on compensation networks are still desirable. Wireless power transmitters and receivers with greater efficiency are still desirable. Wireless power transmitters with more flexible requirements for alignment and spacing between them are still desirable.

[0009] The field of power transmission related to consumer products is becoming increasingly important. In the automotive sector, wiring harnesses have become a crucial and expensive subsystem of vehicles. The automotive wiring harness market is projected to exceed US$77 billion within the next decade. In an era focused on the gasoline mileage of internal combustion engine vehicles, their carbon emissions, and the range of electric vehicles, the cost, weight, and power transmission efficiency of these wiring harnesses have become major concerns in vehicle design. Given that materials and components account for approximately 57% of the cost of automobile manufacturing, these concerns are understandable.

[0010] As battery pack technology steadily improves to provide higher energy density battery packs, consumer demand for more user-assistance electronics and electric drive systems integrated into vehicles also increases. This places greater demands on battery packs, vehicle weight, cost, and power transmission efficiency. In the 1990s, the automotive industry proposed higher voltage battery pack systems, partly in hopes of reducing wiring harness weight.

[0011] Much effort has been made to reduce the amount of expensive copper used in wire harnesses, and there is progress toward using cheaper aluminum. This trend is also driven by the hope of saving approximately 40 lbs of weight in a typical automobile. This trend toward aluminum has its own problems, partly due to the fact that aluminum's resistivity is 1.58 times that of copper. Aluminum also suffers from a phenomenon called creep that causes connections to loosen. In addition, aluminum oxidizes, making protective measures for connections necessary. Some types of wire harnesses still require copper, and any connection between copper and aluminum introduces current potential problems.

[0012] There is clearly a need for an alternative to vehicle wiring harnesses that reduce the amount of expensive copper, provide flexibility regarding voltage, avoid the problems associated with aluminum, and reduce weight.

[0013] At the same time, there is a need to improve the efficiency of power transmission technology to keep up with the rapid progress of battery technology, which in turn is promoted by the development in the field of electric vehicles.

[0014] These requirements are not limited to the automotive sector but also relate to, for example, the field of solar power transmission, and, with a certain modification, also apply to other consumer home appliances (such as computers and television monitors). Power conditioning units for optimally extracting power from sources with different voltages are now widely used, but they are typically subject to a limited degree of control. This, in turn, prevents the optimization of power transmission efficiency.

[0015] The aforementioned examples and related limitations of the related art are intended to be illustrative and non-exclusive. Those familiar with the art will understand other limitations of the related art after reading the specification and studying the diagrams. [Summary of the Invention]

[0016] In a first embodiment, a dual-mode near-field resonant wireless power transmission system configured to simultaneously perform capacitive power transmission and inductive power transmission at a resonant power signal oscillation frequency according to an adjustable transmission mode ratio is presented. The system includes: a transmitter subsystem including a transmitter antenna subsystem and a power signal tuner module configured to adjust the transmission mode ratio by adjusting a power signal provided by the tuner module to the transmitter antenna subsystem; and a receiver subsystem including a receiver antenna subsystem configured to receive power from the transmitter antenna subsystem at the transmission mode ratio.

[0017] The tuner module can be configured to adjust the power signal by adjusting a phase difference between the current and voltage of the power signal supplied to the transmitter antenna subsystem. The transmitter subsystem may further include a controller and at least one sensor, wherein the controller is configured to receive sensor information from the at least one sensor and to automatically provide a tuning command to the tuner module based on the sensor information; and the tuner module is configured to adjust the phase difference between the current and voltage of the power signal supplied to the transmitter antenna subsystem according to the tuning command.

[0018] The at least one sensor may be mounted on the transmitter subsystem. In other embodiments, the at least one sensor may be mounted on the receiver subsystem and the controller may be configured to wirelessly receive sensor information. The at least one sensor may be one of a power load sensor, a transmission power sensor, a surrounding object detector, and a distance detector mounted for detecting a distance between the transmitter antenna and the receiver antenna.

[0019] The resonant power signal oscillation frequency can vary freely within a predetermined frequency band. This predetermined frequency band may be an Industrial, Scientific, and Medical (ISM) band. The system can be demodulated to allow the resonant power signal oscillation frequency to vary to a degree that is opposite to the constraints of the predetermined frequency band.

[0020] In a further embodiment, a wireless method is provided for transmitting power in dual modes at a resonant power signal oscillation frequency according to an adjustable transmission mode ratio. The method includes: providing a transmitter subsystem comprising a power signal tuner module and a transmitter antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a receiver subsystem comprising a receiver antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a power signal from the tuner module to the transmitter antenna subsystem at the power signal oscillation resonant frequency; adjusting the transmission mode ratio by adjusting the power signal from the tuner module to the transmitter antenna subsystem; and receiving the transmitted power at the power signal oscillation resonant frequency via the receiver antenna subsystem at the transmission mode ratio in the receiver subsystem. Adjusting the transmission mode ratio may include adjusting a phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem.

[0021] The transmitter subsystem may further include a controller and at least one sensor, and the tuner module may adjust the phase difference between the current and the voltage based on sensor information received by the controller from the at least one sensor via a command from the controller. The command from the controller may be automatically sent to the tuner module after the sensor information is received by the controller; and the tuner module may automatically execute the command from the controller to change the phase difference.

[0022] The method may further include allowing the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an Industrial, Scientific, and Medical (ISM) band. Providing a transmitter subsystem may include providing a transmitter subsystem that demodulates to a degree that allows the resonant power signal oscillation frequency to vary within the opposite limit of the predetermined frequency band.

[0023] In a further embodiment, a dual-mode near-field resonant wireless power transmission system is provided, configured to simultaneously perform capacitive power transmission and inductive power transmission at a variable resonant power signal oscillation frequency according to an adjustable transmission mode ratio of capacitive power transmission to inductive power transmission. The system includes: a transmitter subsystem including a transmitter antenna and a power signal tuner module, wherein the power signal tuner module adjusts the transmission mode ratio by adjusting a power signal supplied to the transmitter antenna subsystem via the power signal tuner module; and a receiver subsystem including a receiver antenna subsystem to receive power from the transmitter antenna according to the transmission mode ratio.

[0024] The system transmits information between the transmitter antenna subsystem and the receiver antenna subsystem via the transmitter antenna and the receiver antenna of one of the receiver antenna subsystems. The system may further include a modulator for modulating the information onto an information bearer signal and providing the information bearer signal to one of the transmitter antenna subsystems. The system can modulate the information onto an information bearer signal and provide the information bearer signal to the transmitter antenna subsystem. The modulator may be configured to modulate the information bearer signal of the transmitter antenna subsystem according to the information. The power signal tuner module may include the modulator.

[0025] The information-bearing signal may have a frequency different from the oscillation frequency of the variable resonant power signal. The modulator may modulate the information-bearing signal by any of frequency modulation, amplitude modulation, and phase modulation. The information-bearing signal may be modulated such that the oscillation frequency of the variable power signal is a harmonic of a frequency of the information-bearing signal. The information-bearing signal may be modulated to a harmonic of the power signal. The modulated signal provided to the transmitter antenna subsystem may be the power signal.

[0026] The modulator can modulate one of the reflection characteristics of the receiver antenna and transmit the information from the receiver antenna subsystem to the transmitter antenna subsystem by modulating the reflection characteristics of the receiver antenna according to the information. The modulated reflection characteristic of the receiver antenna may be one of the impedances of the receiver antenna.

[0027] This system can transmit information from the receiver subsystem to the transmitter subsystem by modulating the reflection of a signal from the transmitter subsystem by the receiver antenna. The receiver subsystem can modulate the reflection characteristics of the receiver antenna. The receiver subsystem can modulate the impedance of the receiver antenna.

[0028] An electrical load may exist at one of the outputs of the receiver subsystem; and the information may include one or more of the presence of the electrical load, the charging level of the electrical load, a power transmission efficiency, the charging rate of the electrical load, the state of the electrical load, the presence of a voltage on the electrical load, the charging capacity of the electrical load, and the remaining charging time of the electrical load.

[0029] The system can transmit digital information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The system can also transmit analog information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The receiver subsystem can be configured to transmit power to a subsequent receiver subsystem. The receiver may further include a rectifier, which includes a phase shifter.

[0030] In a further embodiment, a dual-mode resonant near-field radio frequency power delivery system is provided, comprising a plurality of power transmission-receiver modules for simultaneously performing capacitive power delivery and inductive power delivery via a power signal at a power signal frequency according to an adjustable transmission mode ratio, wherein each of the plurality of power transmission-receiver modules is in wired communication with a transmitter-receiver resonator disposed to exchange power with at least one of the plurality of power transmission-receiver modules.

[0031] One of the plurality of power transmission-receiver modules may include a power signal tuner module that can be adjusted to change the transmission mode ratio by adjusting the power signal provided by the power signal tuner module to a transmitter-receiver resonator of the first wired communication of the plurality of power transmission-receiver modules. At least one of the plurality of power transmission-receiver modules may include a modulator configured to modulate information onto a radio frequency signal exchanged between a transmitter-receiver resonator associated with the at least one wired communication of the plurality of power transmission-receiver modules and a transmitter-receiver resonator of any other wired communication of the plurality of power transmission-receiver modules.

[0032] The modulator may be any one of an amplitude modulator, a frequency modulator, and a phase modulator. The information may include one or both of digital information and analog information. The radio frequency signal modulated by the modulator may be the power signal. The radio frequency signal modulated by the modulator may have a frequency different from the frequency of the power signal. The radio frequency signal modulated by the modulator may have a frequency that is a harmonic of the frequency of the power signal. The frequency of the power signal may be a harmonic of the frequency of the modulated signal.

[0033] The modulator may be configured to modulate the reflection characteristics of one of the associated wire-connected transmitter-receiver resonators according to the information to apply the information to a signal reflected by the wire-connected transmitter-receiver resonator. The modulator may be configured to modulate a signal provided to the associated transmitter-receiver resonator according to the information. The power signal tuner of the first of the plurality of power transmission-receiver modules may include the modulator. Each of the power transmission-receiver modules may include a compensation network and the compensation network may include the modulator. At least one of the power transmission-receiver modules may include a radio frequency oscillator that provides a signal at the power signal frequency to one of the at least one power transmission-receiver module, and the radio frequency oscillator may include the modulator.

[0034] Each of the plurality of power transmission-receiver modules can be reconfigured between a power transmitter mode and a power receiver mode. Each of the power transmission-receiver modules may include a differential self-synchronizing RF power amplifier / rectifier capable of reconfiguring between an amplifier state and a rectifier state corresponding to the power transmitter mode and the power receiver mode of the power transmission-receiver module, respectively. The differential self-synchronizing RF power amplifier / rectifier may be a differential switching mode self-synchronizing RF power amplifier / rectifier. Each of the power transmission-receiver modules may include a controller, and the reconfiguration may be controlled by the controller. Each differential self-synchronizing RF power amplifier / rectifier may include a phase shifter that can be adjusted by the controller to reconfigure the differential self-synchronizing RF power amplifier / rectifier between the amplifier state and the rectifier state.

[0035] When a power load is present at the output of one of the plurality of power transmission-reception modules in the receiver mode, the information may include one or more of the presence of the power load, the charging level of the power load, the power transmission efficiency, the charging rate of the power load, the state of the power load, the presence of a voltage on the power load, the charging capacity of the power load, and the remaining charging time of the power load.

[0036] In a further embodiment, a near-field radio frequency method is provided for transmitting power via a power signal at a power signal frequency, the method comprising: providing a dual-mode resonant near-field radio frequency power transmission system including a plurality of power transmission-receive modules, wherein each of the plurality of power transmission-receive modules is in wire communication with a transmitter-receiver resonator disposed to exchange power with at least another of the plurality of power transmission-receive modules; and operating the power transmission system to simultaneously perform capacitive power transmission and inductive power transmission according to an adjustable transmission mode ratio.

[0037] The first of the plurality of provided power transmission-reception modules may include a power signal tuner module; and operating the power transmission system may include changing the transmission mode ratio by adjusting the power signal tuner module. Providing the power transmission system may include providing at least one power transmission-reception module among the plurality of power transmission-reception modules that is wired to an associated transmitter-receiver resonator and has a modulator, and operating the power transmission system may include: exchanging a radio frequency signal between the associated transmitter-receiver resonator and a transmitter-receiver resonator that is wired to at least another of the plurality of power transmission-reception modules; and modulating information onto the exchanged radio frequency signal. When a power load is present at one of the outputs of one of the plurality of power transmission-reception modules, the information may include (e.g., but not limited to) the presence of the power load, a charging level of the power load, a power transmission efficiency, a charging rate of the power load, a state of the power load, the presence of a voltage on the power load, a charging capacity of the power load, and one or more of the remaining charging time for the power load.

[0038] The information can be modulated onto the switched radio frequency signal by amplitude modulation, frequency modulation, or phase modulation. Modulating the information onto the switched radio frequency signal may include modulating digital information or analog information onto the switched radio frequency signal.

[0039] Modulating the information onto the switched radio frequency signal may include modulating the information onto the power signal. Modulating the information onto the switched radio frequency signal may include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating the information onto the switched radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the switched radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

[0040] Modulating the information onto the switched radio frequency signal may include modulating the reflection characteristics of one of the associated wire-connected transmitter-receiver resonators according to the information to apply the information to a signal reflected by the wire-connected transmitter-receiver resonator. Modulating the information onto the switched radio frequency signal may include modulating the signal provided to one of the associated transmitter-receiver resonators according to the information.

[0041] The method may include operating the power signal tuner module of the first of the plurality of power transmission-reception modules to modulate the information onto the switched radio frequency signal. Each of the power transmission-reception modules may include a compensation network and the compensation network may include the modulator, thereby allowing the compensation network to be operated to modulate the information onto the switched radio frequency signal. At least one of the power transmission-reception modules may include providing a signal at the power signal frequency to one of the radio frequency oscillators of the at least one power transmission-reception module, and the radio frequency oscillator may include the modulator, thereby allowing the information to be modulated onto the switched radio frequency signal in the oscillator.

[0042] Each of the plurality of provided power transmission-receive modules can be reconfigured between a power transmitter mode and a power receiver mode; and the method may further include reconfiguring at least two of the plurality of power transmission-receive modules between a power transmitter mode and a power receiver mode to reverse one direction of power transmission between the at least two transmission-receive modules. Each of the provided power transmission-receive modules may include a differential autosynchronous radio frequency power amplifier / rectifier capable of reconfiguring between an amplifier state and a rectifier state corresponding to the power transmitter mode and the power receiver mode of the power transmission-receive module, respectively; and the method may include reconfiguring the differential autosynchronous radio frequency power amplifier / rectifier of the at least two transmission-receive modules between the amplifier state and the rectifier state. Each differential self-synchronizing radio frequency power amplifier / rectifier may include a phase shifter that can be adjusted to reconfigure the differential self-synchronizing radio frequency power amplifier / rectifier between amplifier states and rectifier states; and the method may include adjusting one of the phase shifters of each of the differential self-synchronizing radio frequency power amplifiers / rectifiers of the at least two transmit-receive modules.

[0043] In a further embodiment, a near-field resonant wireless power transmission system is provided, comprising: a transmission subsystem including a plurality of substantially decoupled transmitter resonators and corresponding transmitter modules communicating with power signals of each transmitter resonator, each transmitter module including a transmission controller and a power signal source having a power signal oscillation frequency and a power signal phase, each power signal source being controlled by the corresponding transmission controller; one or more receiver subsystems, each including a corresponding receiver resonator; a software lookup table of discrete allowable power signal oscillation frequencies of the power signal sources; and software, which, when loaded into a memory and executed by a controller of any of the transmitter modules, performs the following actions: measuring an input impedance of the corresponding transmitter resonator and a test signal power drawn by the corresponding transmitter resonator; and selecting a frequency for the corresponding power signal source from the lookup table based on the input impedance of the corresponding transmitter resonator and the test signal power drawn by the corresponding transmitter resonator. When executed, the software performs the following actions: measuring the level of the power transmitted through the corresponding transmitter resonator and simultaneously adjusting the phase of a power signal from the corresponding power signal source. These transmitter resonators are substantially decoupled from each other by a grounded shield.

[0044] In a further embodiment, a wireless near-field method is provided for transmitting power from a multi-transmitter subsystem to a single-resonant receiver subsystem at a variable resonant power signal oscillation frequency, the method comprising: providing the multi-transmitter subsystem comprising a plurality of independent transmitter resonators each driven by a corresponding transmitter module capable of being independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all of the transmitter resonators have a common transmission surface; and placing a resonant receiver subsystem, comprising a single receiver resonator overlapping two or more of the transmitter resonators, near the common transmission surface; The method involves measuring the input impedance of each of the transmitter resonators and the power drawn from a test signal by each of the transmitter resonators; setting the power signal of each of the plurality of independent transmitter resonators to one of a closed state and an active state based on the corresponding measured input impedance of the resonators and the power drawn from the test signal by the corresponding transmitter resonators; selecting the power signal oscillation frequency of each active transmitter resonator from among the plurality of preset power oscillation frequencies based on the measured input impedance of each active transmitter resonator; and setting the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator to the substantially maximum phase of power transmission through the transmitter resonator.

[0045] In a further embodiment, a wireless near-field method is provided for transmitting power from a multi-transmitter subsystem to two or more receiver subsystems at a variable resonant power signal oscillation frequency, the method comprising: providing the multi-transmitter subsystem comprising a plurality of mutually independent transmitter resonators each driven by a corresponding transmitter module, each capable of being independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all of the transmitter resonators have a common transmission surface; and placing the two or more resonant receivers, each comprising a single receiver resonator overlapping two or more of the transmitter resonators, close to the common transmission surface. The subsystem measures the input impedance of each of the transmitter resonators and the power drawn from a test signal by each of the transmitter resonators; sets the power signal of each of the plurality of independent transmitter resonators to one of a closed state and an active state based on the corresponding measured resonator input impedance and the power drawn from a test signal by the corresponding transmitter resonators; selects the power signal oscillation frequency of each active transmitter resonator from among the plurality of preset power oscillation frequencies based on the measured input impedance of each active transmitter resonator; and sets the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting the phase of the power signal applied to each corresponding transmitter resonator to the substantially maximum phase of power transmission through the transmitter resonator.

[0046] In a further embodiment, a near-field wireless system for transmitting power from a photovoltaic cell to an electrical load is provided. The system includes: a transmission module that is in wired communication with the photovoltaic cell, the transmission module being configured to convert the power from the photovoltaic cell into an oscillating power signal having an oscillation frequency; a transmitter resonator that is in wired communication with the transmission module and is configured to resonate at the oscillation frequency; a receiver resonator that is configured to resonate at the oscillation frequency and is arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; and a receiver module that is in wired communication with the receiver resonator, the receiver module being configured to receive power from the receiver resonator and to present the received power in direct current form to the electrical load via wired communication.

[0047] The transmission module may include a power amplifier configured to modulate the power received from the photovoltaic cell according to the oscillation frequency. The transmission module may include an oscillator configured to provide the oscillation frequency to the power amplifier. The transmission module may include a controller and one or more sensors, the controller being configured to change the oscillation frequency based on first information from at least one of the one or more sensors. The transmission module may include a transmission tuning network configured to change at least one phase of the power provided by the transmission module to the transmitter resonator based on second information from at least one of the one or more sensors under the control of the controller.

[0048] The system may include a power conditioning unit electrically connected between the photovoltaic cell and the transmission module and configured to adapt the power from the photovoltaic cell to a power conditioning unit in a format compatible with the transmission module. The transmission module may include a small-signal electronic circuit system, and the power conditioning unit may be further configured to provide power to the small-signal electronic circuit system. The transmitter resonator may be disposed on a surface of the photovoltaic cell opposite to one of the cell's active solar radiation receiving surfaces. The transmitter resonator has a surface area that includes at least a major portion of the area of ​​the cell's active solar radiation receiving surface.

[0049] The transmitter resonator may have a planar region smaller than that of the receiver resonator. The receiver resonator may be positioned and configured to receive power from the further transmitter resonator at the resonant frequency via at least one of capacitive coupling and magnetic induction.

[0050] In a further embodiment of a near-field wireless system for transmitting power from a photovoltaic cell array to a power load, the system includes: a first plurality of transmission modules, each transmission module being wired to a corresponding photovoltaic cell in the array, each transmission module being configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmission resonator being wired to a corresponding transmission module from the first plurality of transmission modules and being configured to resonate at the oscillation frequency; a single receiver resonator being configured to resonate at the oscillation frequency and being positioned to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a receiver module being wired to the receiver resonator, the receiver module being configured to receive power from the receiver resonator and present the received power in direct current form to the power load via wired communication.

[0051] Each of the first plurality of transmission modules may include a power amplifier configured to modulate the power received from the corresponding photovoltaic cell according to the oscillation frequency. Each of the first plurality of transmission modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each of the first plurality of transmission modules may further include a controller and one or more sensors, the controller being configured to change the oscillation frequency based on first information from at least one of the one or more sensors. Each of the first plurality of transmission modules may include a transmission tuning network configured to change at least one phase of the power provided by the transmission module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

[0052] The system may include a third plurality of power conditioning units, each of which is electrically connected between the corresponding photovoltaic cell and the corresponding transmission module and configured to adjust the power from the corresponding photovoltaic cell to a format compatible with the corresponding transmission module. Each of the first plurality of transmission modules may include a small-signal electronic circuit system, and the corresponding power conditioning unit may be further configured to provide power to the small-signal electronic circuit system. Each of the second plurality of transmitter resonators may be disposed on a surface of the corresponding photovoltaic cell opposite to one of the cell's active solar radiation receiving surfaces.

[0053] In a further embodiment of a near-field wireless system for transmitting power from a photovoltaic cell array to a power load, the system includes: a first plurality of transmission modules, each transmission module being in wired communication with a corresponding photovoltaic cell in the array, each transmission module being configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmission resonator being in wired communication with a corresponding transmission module from the first plurality of transmission modules and being configured to resonate at the oscillation frequency; and a third plurality of receivers. A resonator, configured to resonate at the oscillation frequency, wherein each of the third plurality of receiver resonators is configured to receive power from a corresponding transmitter resonator among the second plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each receiver module being wired to a corresponding receiver resonator among the third plurality of receiver resonators, wherein the receiver module is configured to receive power from the corresponding receiver resonator and to present the received power in DC form to the power load via wired communication.

[0054] Each of the first plurality of transmission modules may include a power amplifier configured to modulate the power received from the corresponding photovoltaic cell according to the oscillation frequency. Each of the first plurality of transmission modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each of the first plurality of transmission modules may further include a controller and one or more sensors, the controller being configured to change the oscillation frequency based on first information from at least one of the one or more sensors. Each of the first plurality of transmission modules may include a transmission tuning network configured to change at least one phase of the power provided by the transmission module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

[0055] The system may further include a fifth plurality of power conditioning units, each of which is electrically connected between the corresponding photovoltaic cell from the solar cell array and the corresponding transmission module from the first plurality of transmission modules, and is configured to adjust the power from the corresponding photovoltaic cell to a format compatible with the corresponding transmission module. Each transmission module from the first plurality of transmission modules may include a small signal electronic circuit system, and the corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small signal electronic circuit system. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of the corresponding photovoltaic cell from the photovoltaic cell array opposite to one of the active solar radiation receiving surfaces of the cell.

[0056] In a further embodiment, a near-field wireless system for transmitting power from a photovoltaic cell array to a power load is presented. The system includes: a first plurality of transmission modules, each transmission module being in wired communication with a corresponding photovoltaic cell in the array, each transmission module being configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmitter resonator being in wired communication with a corresponding transmission module from the first plurality of transmission modules and being configured to resonate at the oscillation frequency; a third... A plurality of receiver resonators, which are fewer in number than the plurality of transmitter resonators and are configured to resonate at the oscillation frequency, wherein each receiver resonator among the third plurality of receiver resonators is arranged to receive power from a portion of the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each receiver module being wired to a corresponding receiver resonator, the receiver module being configured to receive power from the corresponding receiver resonator and to present the received power in DC form to the power load via wired communication.

[0057] Each of the first plurality of transmission modules may include a power amplifier configured to modulate the power received from the corresponding photovoltaic cell according to the oscillation frequency. Each of the first plurality of transmission modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each of the first plurality of transmission modules may further include a controller and one or more sensors, the controller being configured to change the oscillation frequency based on first information from at least one of the one or more sensors. Each of the first plurality of transmission modules may include a transmission tuning network configured to change at least one phase of the power provided by the transmission module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

[0058] The system may include a fifth plurality of power conditioning units, each of which is electrically connected between the corresponding photovoltaic cell from the solar cell array and the corresponding transmission module from the first plurality of transmission modules and is configured to adjust the power from the corresponding photovoltaic cell to a format compatible with the corresponding transmission module.

[0059] Each transmission module from the first plurality of transmission modules may include a small-signal electronic circuit system, and the corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small-signal electronic circuit system. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of the corresponding photovoltaic cell from the photovoltaic cell array opposite to one of the active solar radiation receiving surfaces of the cell.

[0060] In a further embodiment, a method for transmitting power from a photovoltaic cell to an electrical load is provided, the method comprising: converting the power from the photovoltaic cell into an oscillating power signal having an oscillation frequency in a transmission module; transmitting the power to a transmitter resonator configured to resonate at the oscillation frequency and in wired communication with the transmission module; receiving the power in a receiver resonator configured to resonate at the oscillation frequency and arranged to receive the power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving the power in a receiver module in wired communication with the receiver resonator; and presenting the received power as direct current to the electrical load via wired communication.

[0061] In a further embodiment of a method for transmitting power from a photovoltaic cell array to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmission modules; transmitting the power from each of the transmission modules to a corresponding transmission resonator from one of a second plurality of transmission resonators configured to resonate at the oscillation frequency; receiving the power in a receiver resonator configured to resonate at the oscillation frequency and arranged to receive the power from the plurality of transmission resonators via at least one of capacitive coupling and magnetic induction; receiving the power in a receiver module that is in wired communication with the receiver resonator; and presenting the received power as direct current to the electrical load via wired communication.

[0062] In a further embodiment of a method for transmitting power from a photovoltaic cell array to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmission modules; transmitting the power from each of the transmission modules to a corresponding transmission resonator from a second plurality of transmission resonators, wherein each transmission resonator is configured to resonate at the oscillation frequency; receiving the power from each transmission resonator in a corresponding receiver resonator configured to resonate at the oscillation frequency, wherein each receiver resonator is further configured and arranged to receive the power from the transmission resonator via at least one of capacitive coupling and magnetic induction; receiving the power from each receiver resonator in a corresponding receiver module that is in wired communication with the receiver resonator; and presenting the received power as direct current to the electrical load via wired communication.

[0063] In a further embodiment of a method for transmitting power from a photovoltaic cell array to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmission modules; transmitting the power from each of the transmission modules to a transmitter resonator from one of a second plurality of transmitter resonators, wherein each transmitter resonator is configured to resonate at the oscillation frequency; receiving the power from each transmitter resonator in any proximity receiver resonator among a third plurality of receiver resonators configured to resonate at the oscillation frequency, wherein each receiver resonator is further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; sharing the received power among the third plurality of receiver resonators; and presenting the received power in direct current form from one or more of the third plurality of receiver resonators to the electrical load via wired communication corresponding to one or more receiver modules. The method may further include converting a voltage and a current of the power from each photovoltaic cell into a voltage and a current suitable for the corresponding transmission module before converting the power from each photovoltaic cell into an oscillating power signal.

[0064] A power transmission system is provided for supplying power from a DC power source to a power load. The system includes: a radio frequency power amplifier wired to the power source and configured to convert a DC voltage from the source into an AC voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier wired to the power load and radio frequency communicating with the power amplifier, the rectifier being configured to receive power transmitted from the amplifier; and a receiver controller communicating with the rectifier, the receiver controller being configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting a current-voltage phase characteristic of the rectifier. The rectifier may be a differential self-synchronizing radio frequency rectifier.

[0065] The receiver controller can be configured to automatically adjust the current-voltage phase characteristics of the rectifier. The power transmission system may further include a load management system that is in wired communication with the load and whose power signal is disposed between the load and the rectifier. The load management system is configured to increase the efficiency of the power transmission by adjusting an input impedance of the rectifier. The load management system can be configured to automatically adjust the current-voltage phase characteristics of the rectifier.

[0066] The power transmission system may further include a transmitter controller in communication with the amplifier, the transmitter controller being configured to increase the efficiency of the power transmission by adjusting a current-voltage phase characteristic of the amplifier. The transmitter controller may be configured to automatically adjust the current-voltage phase characteristic of the amplifier to increase the efficiency of the power transmission.

[0067] The power transmission system may further include an oscillator that communicates with the amplifier and the transmitter controller. The transmitter controller may be configured to adjust the oscillation frequency via the oscillator.

[0068] The power amplifier can communicate directly with the adjustable-phase RF rectifier via wired RF. The power amplifier can also communicate wirelessly with the adjustable-phase RF rectifier via near-field RF. The power delivery system may include a transmitter resonator that communicates with the power amplifier via wired RF and a receiver resonator that communicates with the rectifier via wired RF. The transmitter resonator and receiver resonator can communicate wirelessly with each other via near-field RF. The power amplifier can communicate with the rectifier via at least one of capacitive near-field wireless RF and inductive near-field wireless RF. The power amplifier can communicate with the rectifier via dual-mode near-field wireless RF.

[0069] The DC power supply may include a rechargeable battery pack and the load may include an electric motor. The load may include a computer monitor. One resonant structure of the system may include at least one conductive mechanical load-bearing structural component of the system.

[0070] The system may further include a power conditioning unit electrically disposed between the source and the power transmission system, the power conditioning unit being configured to adjust at least one of a current and a voltage from the source to improve the efficiency of the power transmission.

[0071] A method for transmitting power from a DC power source to a power load is further provided, the method comprising: providing a power transmission system in wired communication with the power source, the power transmission system including a radio frequency power amplifier in radio frequency communication with an adjustable phase radio frequency rectifier, the adjustable phase radio frequency rectifier being in wired contact with the power load; converting the power from the DC power source into a radio frequency oscillating power signal in the amplifier; converting the radio frequency oscillating power signal into a DC power signal in the rectifier; and adjusting the efficiency of the power transmission by adjusting a current-voltage phase characteristic of the rectifier. Providing the adjustable phase radio frequency rectifier may include providing a differential self-synchronizing radio frequency rectifier.

[0072] The method may further include adjusting the efficiency of the power delivery by adjusting one of the DC equivalent input resistances of the amplifier. Providing the power delivery system may include a load management system that provides wired communication between the rectifier and the load. Adjusting the DC equivalent input resistance of the amplifier may include adjusting one of the input impedances of the rectifier by adjusting the load management system. Adjusting the load management system may include automatically adjusting the load management system.

[0073] The method may further include adjusting the efficiency of the power transmission by adjusting the current-voltage phase characteristics of one of the power amplifiers. The power transmission system may include providing a transmitter controller that communicates with the power amplifier to control it. The adjustment of the current-voltage phase characteristics of the power amplifier may be performed by the transmitter controller. The adjustment of the current-voltage phase characteristics of the power amplifier may be performed automatically by the transmitter controller.

[0074] The method may further include adjusting the efficiency of the power transmission by changing the oscillation frequency of one of the power amplifiers.

[0075] The provision of a power transmission system may include a receiver controller that communicates with the rectifier to control the rectifier. The adjustment of the current-voltage phase characteristics of the rectifier may be performed by the receiver controller. The adjustment of the current-voltage phase characteristics of the rectifier may be performed automatically by the receiver controller.

[0076] The provision of the power transmission system may include the power amplifier providing direct wired radio frequency communication with the adjustable phase radio frequency rectifier. The provision of the power transmission system may include the power amplifier providing wireless near-field radio frequency communication with the adjustable phase radio frequency rectifier.

[0077] The power delivery system may include a transmitter resonator providing wired radio frequency communication with the power amplifier and a receiver resonator providing wired radio frequency communication with the radio frequency rectifier. The method may further include the transmitter resonator and receiver resonator operating wireless near-field radio frequency communication with each other. The power delivery system may include the power amplifier providing at least one of capacitive near-field wireless radio frequency communication and inductive near-field wireless radio frequency communication with the rectifier. The power delivery system may include the power amplifier providing dual-mode wireless near-field communication with the rectifier.

[0078] The method may further include: providing a power conditioning unit electrically disposed between the power source and the power transmission system; and adjusting the power conditioning unit to adjust at least one of a current and a voltage from the source to improve the efficiency of the power transmission.

[0079] A method for transmitting power from a DC power source to an electrical load is further provided, the method comprising: providing a power transmission system in wired communication with the power source, the power transmission system including an oscillator capable of oscillating at an oscillation frequency; a power amplifier and a transmitter tuning network, both under the control of a transmitter controller; and a receiver tuning network and a load management system, both under the control of a receiver controller, the load management system in wired communication with the electrical load; converting the power from the power source into an oscillating power signal having the oscillation frequency in the power amplifier; transmitting the power signal from the power amplifier to the load management system via the transmitter tuning network and the receiver tuning network under the control of the transmitter controller; adjusting at least one of the oscillation frequency, an input DC equivalent resistance of the power amplifier, the transmitter tuning network, the receiver tuning network, and the load management system to change a power transmission rate; and presenting the power received by the load management system in DC form to the electrical load via wired communication.

[0080] Transmitting the power signal via the transmitter tuning network and the receiver tuning network may include transmitting the power via wired communication. Transmitting the power signal via the transmitter tuning network and the receiver tuning network may include transmitting the power via wireless communication. Transmitting the power via wireless communication may include transmitting the power via near-field wireless communication. Transmitting the power via near-field wireless communication may include transmitting the power via at least one of capacitive coupling and inductive coupling.

[0081] The power transmission from a DC power source may include power transmission from at least one solar cell. The power transmission from a DC power source may include power transmission from at least one solar cell array. The power transmission from a DC power source may include power transmission from a power source having one of different voltages.

[0082] In another embodiment, an electric system includes: a mechanical load-bearing structure having a first conductive portion; an electrical load; and a power transmission system including at least one radio frequency resonator configured for near-field wireless power transmission, wherein the resonator at least partially includes the first conductive portion. The electric system may further include a rechargeable battery pack, and the electrical load may include an electric motor. The electric system may be an electric vehicle, and the mechanical load-bearing structure may include a housing of the vehicle. The electric system may be a display monitor, and the mechanical load-bearing structure may be at least one of a frame and a base of the monitor.

[0083] The electric system may further include a power source. The power transmission system may include: a radio frequency power amplifier that is wired to the power source and configured to convert a DC voltage from the source into an AC voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier that is wired to the power load and radio frequency to the power amplifier, the rectifier being configured to receive power transmitted from the amplifier; and a receiver controller that communicates with the rectifier, the receiver controller being configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting a current-voltage phase characteristic of the rectifier.

[0084] In another embodiment, an apparatus includes: a mechanical load-bearing structure having a conductive first portion; a power source; a power load; and a power transmission system including: a radio frequency power amplifier wired to the power source and configured to convert a DC voltage from the source into an AC voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier wired to the power load and radio frequency communicating with the power amplifier, the rectifier being configured to receive power transmitted from the amplifier; and a receiver controller communicating with the rectifier, the receiver controller being configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting a current-voltage phase characteristic of the rectifier; wherein the conductive first portion is disposed to carry a radio frequency signal from at least one of the amplifier and to the rectifier.

[0085] The device may further include a load management system that is wired to the load and electrically located between the load and the rectifier, the load management system being configured to increase the efficiency of power transmission by adjusting an input impedance of the rectifier. The device may further include a transmitter controller that communicates with the amplifier, the transmitter controller being configured to increase the efficiency of power transmission by adjusting a current-voltage phase characteristic of the amplifier. The device may further include an oscillator that communicates with the amplifier and the transmitter controller, wherein the transmitter controller is configured to adjust the oscillation frequency via the oscillator.

[0086] The power amplifier can communicate directly with the rectifier via the conductive first portion using wired radio frequency (RF). The power amplifier can also communicate wirelessly with the rectifier using near-field radio frequency (NFC). The power delivery system may include a transmitter resonator communicating with the power amplifier via wired RF and a receiver resonator communicating with the rectifier via wired RF, and one of the transmitter resonator and the receiver resonator may include the conductive first portion. The transmitter resonator and the receiver resonator can communicate wirelessly with each other using NFC. The power amplifier can communicate with the rectifier using at least one of capacitive NFC and inductive NFC. The power amplifier can communicate with the rectifier using dual-mode NFC. The DC power supply may include a rechargeable battery pack and the load may include an electric motor.

[0087] In some embodiments, a sealed bidirectional power transmission circuit device includes a plurality of terminals disposed for electrical communication with a device outside the sealed device. The sealed device includes, within a sealed interior: a multi-terminal power switching device having at least one DC terminal, at least one AC terminal, and at least one control terminal. The multi-terminal power switching device is adjustable between an amplification state and a rectification state and is configured to bidirectionally transmit a DC voltage and a DC current via the at least one DC terminal and bidirectionally transmit a radio frequency power signal having an amplitude, a frequency, and a phase via the at least one AC terminal; a phase, frequency, and duration cyclic adjustment circuit that is wiredly data-communicating with a controller. The phase, frequency, and duration cyclic adjustment circuit is wiredly electricalally communicating with the power switching device via the at least one control terminal and is configured to establish a radio frequency oscillation signal having the frequency and phase of the radio frequency power signal at the at least one control terminal of the power switching device and adjust the power switching device between the amplification state and the rectification state by adjusting the phase of the radio frequency oscillation signal under the command of the controller. In some embodiments, the controller may be housed within the sealed interior of the sealed bidirectional power transmission circuit device. The plurality of terminals of the sealed power transmission circuit device may include terminals for data communication between the controller and devices outside the sealed interior.

[0088] The radio frequency power signal may have an action time cycle, and the phase, frequency, and action time cycle adjustment circuit may be further configured to adjust the action time cycle of the radio frequency power signal by adjusting one of the action time cycles of the radio frequency oscillation signal. The phase, frequency, and action time cycle adjustment circuit may include a radio frequency oscillator for generating the radio frequency oscillation signal upon instruction from the controller.

[0089] The sealed power transmission circuit device may further include, within the sealed interior, a tuning network that communicates with the controller via wired data communication and with the power switching device via the at least one AC terminal. The tuning network is configured to adjust the radio frequency power signal to a tuned radio frequency power signal upon instruction from the controller. The bidirectional power transmission circuit device may include a modulator configured to modulate information onto the radio frequency power signal. The modulator may include the tuning network. The modulator may be configured to modulate the radio frequency power signal using information provided by the controller. The tuning network may include a harmonic termination network circuit configured to suppress harmonics of the radio frequency oscillation signal in the radio frequency power signal. The harmonic termination network may include one or more inductors and one or more of a first harmonic termination, a second harmonic termination, and a third harmonic termination. The sealed power transmission circuit device may further include, within the sealed interior, an amplitude / frequency / phase detector that communicates with the controller via wired data. This amplitude / frequency / phase detector is configured to communicate with the tuning network via wired data and to determine the amplitude, frequency, and phase of any radio frequency power signal transmitted between the tuning network and an AC load / source outside the sealed device. The tuning network may further include one or more of a compensation network, a matching network, and a filter.

[0090] The phase, frequency, and duration cycle adjustment circuit can be configured to receive commands from the controller based on measurement data transmitted to the controller via the amplitude / frequency / phase detector. The phase, frequency, and duration cycle adjustment circuit can be configured to adjust the radio frequency oscillation signal based on a feedback signal received directly from the amplitude / frequency / phase detector. The tuning network may include a voltage-current tuner for adjusting a phase difference between a voltage and a current of the tuned radio frequency power signal based on measurement data from the amplitude / frequency / phase detector when the power switching device is in the amplified state.

[0091] The sealed power transmission circuit device may further include, within the sealed interior, a power management circuit for wired communication between the power switching device and an external DC power source / load. This power management circuit is configured to impedance match the power switching device and the external DC power source / load and to adjust the DC power transmitted between the power switching device and the DC power source / load based on a feedback signal received directly from the amplitude / frequency / phase detector. In other embodiments, the sealed power transmission circuit device may further include, within the sealed interior, a power management circuit for wired data communication with the controller and wired communication between the power switching device and an external DC power source / load. This power management circuit is configured to impedance match the power switching device and the external DC power source / load and to adjust the DC power transmitted between the power switching device and the DC power source / load based on measurement data transmitted to the controller via the amplitude / frequency / phase detector.

[0092] The sealed power transmission circuit device may further include, within the sealed interior, a voltage / current sensor that communicates with the controller via wired data communication. The voltage / current sensor is positioned to determine a DC voltage and DC current transmitted between the power switching device and the power management circuit. The phase, frequency, and duration cycle adjustment circuit may be configured to receive instructions from the controller based on measurement data transmitted to the controller via the voltage / current sensor. In other embodiments, the phase, frequency, and duration cycle adjustment circuit may be configured to adjust the radio frequency oscillation signal based on a feedback signal received directly from the voltage / current sensor.

[0093] The sealed power transmission circuit device may further include, within the sealed interior, a memory that communicates with the controller, the amplitude / frequency / phase detector, and the voltage / current detector via wired data communication, wherein the memory is configured to receive and store measurement data from the two detectors and to provide the signal data from the two detectors to the controller.

[0094] The sealed power transmission circuit device may further include within the sealed interior a power management circuit for wired communication between the power switching device and the AC power source / load outside the sealed device. The power management circuit is configured to match an amplitude, a frequency, and a phase of the power switching device and the external AC power source / load, and to adjust the AC power transmitted between the power switching device and the AC power source / load based on a feedback signal received directly from the amplitude / frequency / phase detector.

[0095] The sealed power transmission circuit device may further include within the sealed interior a power management circuit that communicates with the controller via wired data and with the AC power source / load outside the sealed device via wired electrical communication. The power management circuit is configured to match an amplitude, a frequency, and a phase of the power switching device and the external AC power source / load and to adjust the AC power transmitted between the power switching device and the AC power source / load based on measurement data transmitted to the controller via the amplitude / frequency / phase detector.

[0096] The sealed power transmission circuit device may further include a voltage / current detector that communicates with the controller via wired data within the sealed interior. The voltage / current detector is positioned to determine a DC voltage and DC current transmitted between the power switching device and the power management circuit.

[0097] In some embodiments, the phase, frequency, and duration cycle adjustment circuit is configured to receive instructions from the controller based on measurement data transmitted to the controller via the voltage / current sensor. In some embodiments, the phase, frequency, and duration cycle adjustment circuit is configured to adjust the radio frequency oscillation signal based on a feedback signal received directly from the voltage / current sensor.

[0098] The sealed power transmission circuit device may further include, within the sealed interior, a memory that communicates with the controller, the amplitude / frequency / phase detector, and the voltage / current detector via wired data communication, wherein the memory is configured to receive and store measurement data from the two detectors and to provide the signal data from the two detectors to the controller.

[0099] The hermetically sealed power transmission circuit device may further include within the hermetically sealed interior at least one of a Bluetooth communication circuit, a WiFi communication circuit, a Zigbee communication circuit, and a cellular communication technology circuit for transmitting information between the controller and a device outside the hermetically sealed power transmission circuit device. The communication circuit may have bidirectional wired communication with at least one communication antenna configured to communicate with a device outside the hermetically sealed power transmission circuit device. The antenna for the communication circuit may be housed within the hermetically sealed interior of the hermetically sealed device.

[0100] The bidirectional power transmission circuit device may include a modulator configured to modulate information onto at least one of the radio frequency power signal and the DC voltage. The modulator may include the power switching device. The modulator may be configured to modulate the at least one of the radio frequency power signal and the DC voltage using information provided by the controller. The modulator may further include phase, frequency, and duration-of-use (TOU) cyclic adjustment circuitry.

[0101] In some embodiments, all circuit elements of the bidirectional power transmission circuit device can be monolithically integrated into a silicon single crystal wafer. In some embodiments, at least a portion of the circuit elements of the device can be integrated using flip-chip technology.

[0102] In one particular embodiment, the electronic circuitry of the hermetically sealed bidirectional power transmission circuit device may be implemented in conjunction with at least one photovoltaic cell serving as a DC source / load within a single silicon monocrystalline wafer. In a further embodiment, the electronic circuitry of the hermetically sealed bidirectional power transmission circuit device may be implemented in conjunction with at least one photovoltaic cell serving as a DC source / load 700 and a resonator structure serving as an AC load / source on one surface of the silicon monocrystalline wafer within a single silicon monocrystalline wafer. Antennas for use with Bluetooth, WiFi, Zigbee, and cellular technologies may also be integrated onto the same single silicon monocrystalline wafer.

Implementation Method

[0145] Cross Reference

[0146] This application asserts the rights of U.S. Provisional Application No. 63 / 078,824, filed on September 15, 2020, which is incorporated herein by reference.

[0147] Throughout the following description, specific details are set forth in order to provide a more thorough understanding to those skilled in the art. However, well-known elements may not be shown or described in detail so as not to unnecessarily obscure the invention. Therefore, the description and figures should be regarded as illustrative rather than restrictive.

[0148] One embodiment of the present invention provides a wireless power transmission system comprising a transmitter (also referred to as a primary side) and a receiver (also referred to as a secondary side). Another embodiment of the present invention provides a wireless power transmitter that can be used as part of other wireless power transmission systems. Another embodiment of the present invention provides a wireless power receiver that can be used as part of other wireless power transmission systems. According to some embodiments of the present invention, a transmitter may include a resonator configured to transmit power via inductive power and / or via capacitive power. Similarly, according to some embodiments of the present invention, a receiver may include a resonator configured to receive power via inductive power and / or via capacitive power.

[0149] Figure 1 is a simplified schematic diagram of a wireless power transfer (WPT) system 10 including a primary side 12 and a secondary side 14. The primary side 12 may also be referred to as a transmitter and the secondary side 14 may also be referred to as a receiver. The primary side 12 includes a transmitter module 20 and a transmitter resonator 30 and the secondary side 14 includes a receiver module 40 and a receiver resonator 50.

[0150] Transmitter module 20 receives power, including, for example, direct current (DC) power, as input. Although not depicted, transmitter module 20 may include, for example, an inverter, a transmitter compensation network, and / or other components as further described herein. Transmitter module 20 delivers power, including, for example, alternating current (AC) power, as output to transmitter resonator 30.

[0151] The transmitter resonator 30 receives power from the transmitter module 20 as input and can output a magnetic field 31A (e.g., a time-varying magnetic field) and / or an electric field 31B (e.g., a time-varying electric field). In some embodiments, the transmitter resonator 30 outputs the magnetic field 31A for the purpose of IPT. In some embodiments, the transmitter resonator 30 outputs the electric field 31B for the purpose of CPT. In some embodiments, the resonator 30 simultaneously outputs the magnetic field 31A and the electric field 31B for the purpose of simultaneously transmitting power through CPT and IPT. In some embodiments, the resonator 30 can switch between outputting the electric field 31B for the purpose of CPT, outputting the magnetic field 31A for the purpose of IPT, and simultaneously outputting the magnetic field 31A and the electric field 31B for the purpose of simultaneously transmitting power through CPT and IPT.

[0152] The adjective term "dual-modal" is used herein to describe a system configured for simultaneous capacitive and inductive signal transmission.

[0153] In the presence of magnetic field 31A, a current can be induced in receiver resonator 50 for IPT purposes. In the presence of electric field 31B, an alternating potential can be induced on receiver resonator 50 (or one or more of its antennas).

[0154] When a current is induced in the receiver resonator 50 by the magnetic field 31A, this current can be output to the receiver module 40. Similarly, when an alternating potential is induced on the receiver resonator 50 by the electric field 31B, a current can be induced to flow into the receiver module 40 by the receiver resonator 50.

[0155] Receiver module 40 may receive power (e.g., AC power) as input from receiver resonator 50 and may output power (e.g., DC power) to a load. A load may be a charge for a power storage device (such as a battery pack or supercapacitor). By way of non-limiting examples, the load may include or be a component of an electric bicycle (also referred to as an e-bicycle or e-bike), such as an e-bicycle, car, boat, etc., that is part of a shared bicycle fleet. Although not depicted, receiver module 40 may include, for example, a rectifier, a receiver compensation network, and / or other components as further discussed herein.

[0156] For various reasons, the WPT system 10 can be configured to adjust the ratio ("transmission mode ratio") of the power transmitted from the transmitter module 20 to the receiver module 40 via the CPT to the power transmitted via the IPT from the transmitter module 20 to the receiver module 40. For example, the transmission mode ratio can be adjusted to increase the proportion of power delivered by the CPT when the distance between the transmitter resonator 30 and the receiver resonator 50 increases; to increase the proportion of power delivered by the IPT when a living being (e.g., a human or animal) approaches the WPT system 10; to increase the proportion of power delivered by the CPT when an object (e.g., a metallic object) approaches the WPT system 10; to increase the proportion of power delivered by the CPT when the alignment between the transmitter resonator 30 and the receiver resonator 50 deteriorates; and / or any combination thereof.

[0157] In some embodiments, the delivery mode ratio may be adjusted according to a maximum power point tracking (MPPT) technique, such as (but not limited to) observations and disturbances sometimes used for wind turbines and solar panels (e.g., see S. Dehghani, S. Abbasian and T. Johnson, “Adjustable Load With Tracking Loop to Improve RF Rectifier Efficiency Under Variable RF Input Power Conditions,” IEEE Transactions on Microwave Theory and Techniques, Vol. 64, No. 2, pp. 343-352, February 2016). In some embodiments, the delivery mode ratio may be adjusted according to a machine learning algorithm. For example, in some embodiments, if the WPT system 10 determines that a WPT efficiency is undesirably low, the WPT system 10 may increase the proportion of power delivered via CPT (or IPT). If the WPT efficiency is negatively affected by the increased reliance on CPT (or IPT), the WPT system 10 may reduce its reliance on CPT (or IPT). This procedure can be repeated until a desirable / maximum WPT efficiency is achieved.

[0158] Each of the transmitter resonator 30 and the receiver resonator 50 may include a plurality of antennas 80 configured in various ways.

[0159] Antenna 80 may include any suitable antenna having a high self-inductance and a high self-capacitance, capable of generating both a magnetic field 31A and an electric field 31B (alone and / or simultaneously) for the purposes of CPT and IPT. Figures 2A, 2B and 2C depict non-limiting examples of antennas 80, 180, 280. For purposes herein, a "high self-inductance" is a self-inductance sufficient to allow the antenna to generate a magnetic field suitable for the purposes of IPT. Similarly, for purposes herein, a "high self-capacitance" is a self-capacitance sufficient to allow the antenna to generate an electric field suitable for the purposes of CPT.

[0160] FIG. 2A depicts an antenna 80 according to one embodiment of the present invention. The antenna 80 may comprise any suitable conductive material. For example, the antenna 80 may comprise copper, gold, silver, aluminum, other suitable materials, or a combination thereof. As can be seen from FIG. 2A, the antenna 80 includes an elongated element 80A having a generally planar rectangular (in the XY plane) coil shape that is bent or formed such that the adjacent portion of the elongated element 80A wraps around a rectangular (e.g., square) cross section separated by a gap 80B. Although the gap 80B is depicted as being generally constant along the length of the elongated element 80, this is not mandatory.

[0161] To increase the self-inductance of the antenna 80, the size of the gap 80B can be reduced. To increase the self-capacitance of the antenna 80, the number of bends (e.g., bend 82A) of the elongated element 80A can be increased, the number of corners and edges (e.g., edge 82B) of the elongated element 80A can be increased, the length of the elongated element 80A can be increased, and / or the thickness 80C of the elongated element 80A can be increased.

[0162] FIG. 2B depicts another non-limiting example of an antenna 180 according to another embodiment of the present invention. Antenna 180 is substantially similar to the first antenna 80, except that instead of being bent or formed in the shape of a generally planar rectangular coil, the elongated element 180A is bent or formed in a generally planar serrated shape with square corners, as depicted in FIG. 2B. Like antenna 80, adjacent serrations of the elongated element 180A are separated by a gap 180B. Although the gap 180B is depicted as being generally constant along the length of the elongated element 180, this is not mandatory.

[0163] To increase the self-inductance of the antenna 180, the size of the gap 180B can be reduced. To increase the self-capacitance of the antenna 180, the number of bends (e.g., bend 182A) of the elongated element 180A can be increased, the number of corners and edges (e.g., edge 182B) of the elongated element 180A can be increased, and / or the thickness 180C of the elongated element 180A can be increased.

[0164] FIG. 2C depicts another non-limiting example of an antenna 280 according to another embodiment of the present invention. The antenna 280 is substantially similar to the first antenna 80, except that instead of being bent or formed in the shape of a generally planar rectangular coil, the elongated element 280A is bent or formed in the shape of a generally planar circular shape (in the XY plane) of a hub element 280A having sector elements 280C extending radially outward therefrom. Adjacent sector elements 280C are separated from each other by gaps 280B.

[0165] To increase the self-inductance of antenna 280, the size of gap 280B can be reduced. To increase the self-capacitance of antenna 280, the number of sectors 280C can be increased, the number of corners and edges (e.g., edge 282A) of hub 280A and / or sector 280C can be increased, and / or the thickness 280C of elongated hub 280A and / or sector 280C can be increased.

[0166] Although Figures 2A, 2B, and 2C depict exemplary, non-limiting embodiments of antennas 80, 180, and 280, it should be understood that many other shapes and configurations suitable for antenna 80 may be employed in the resonators described herein. Non-limiting examples of modifications that may be made to the depicted antennas include changing the cross-sectional shape of the elongated elements 80A and 180A to a shape other than rectangle (e.g., triangle, circle, hexagon, etc.), changing the 90° bends 82A and 182A to non-90° or rounded shapes, changing the XY plane shape of the first transmitter antenna 80 to a shape other than rectangle or circle, using non-repeating patterns of bends and corners, etc.

[0167] Although antennas 80, 180, and 280 are described and depicted herein as relatively flat or planar (e.g., with substantially no variation in thickness in the Z direction), this is not mandatory. In some embodiments, antennas 80, 180, and 280 may have a conical concave or conical convex shape, as depicted in Figures 3A and 3B. For example, the antennas herein may have a conical helical shape (not depicted). In some embodiments, antenna 80 may have a rectangular conical helical shape such that the inner winding of antenna 80 is spaced apart from the outer winding of antenna 80 in the Z direction. Such conical shapes allow a resonator to be used for a wider range of resonant frequencies. In other embodiments, the thickness of the first transmitter antenna in the Z direction may vary in other ways.

[0168] For example, antennas 80, 180, and 280 can be configured similarly to the board configuration in a CPT WPT system. For example, in a dual-antenna WPT system according to an embodiment of the present invention, transmitter resonator 30 may include a first transmitter antenna 32 configured parallel to a first receiver antenna 52 of receiver resonator 50, as shown in FIG4A. For CPT purposes, the mutual capacitance between the two antennas 32, 52 provides a path for current to flow forward to the receiver side, and a conductive path (e.g., ground) allows current to flow back to the transmitter side. For IPT purposes, by driving a current through the first transmitter antenna 32, a magnetic field 31A is generated that can induce a current in the first receiver antenna 52. For CPT purposes, a voltage may be applied to the first transmitter antenna 32 to generate a potential difference between the first transmitter antenna 32 and the first receiver antenna 52, thereby generating an electric field 31B.

[0169] The first transmitter antenna 32 may include any suitable antenna capable of generating both a magnetic field 31A and an electric field 31B (alone and / or simultaneously) and having a high self-inductance and a high self-capacitance. For example, the first transmitter antenna may include one of antennas 80, 180, 280 or any other antenna described herein.

[0170] The first receiver antenna 52 may include any suitable antenna capable of having a current induced therein by the magnetic field 31A and (alone and / or simultaneously) a potential difference thereon due to the electric field 31B, having a high self-inductance and a high self-capacitance. In some embodiments, the first receiver antenna 52 may be substantially similar to the first transmitter antenna 32 (e.g., the first receiver antenna 52 may have the same characteristics as any antenna described or depicted herein or otherwise). In some embodiments, antennas 32 and 52 may be different from each other (e.g., the first transmitter antenna 32 may include antenna 80 and the first receiver antenna 52 may include antenna 180).

[0171] In some embodiments, the XY plane area of ​​one of the first transmitter antennas 32 is smaller than the XY plane area of ​​one of the first receiver antennas 52 to improve the coupling between the first transmitter antenna 32 and the first receiver antenna 52.

[0172] Figure 4B depicts another example of a configuration of antennas 80, 180, and 280. Specifically, Figure 4B depicts a four-antenna stack (or four-antenna vertical) WPT system. Each of the transmitter resonator 130 and the receiver resonator 150 includes two antennas. One antenna of the transmitter resonator 30 and one antenna of the receiver resonator 150 together provide a forward path for power, and the other antenna of the transmitter resonator 130 and the other antenna of the receiver resonator 150 together provide a return path for power.

[0173] For the purpose of IPT, a magnetic field is generated by driving a current through the antennas 132 and 134 of the transmitter, which can induce a current in the first and second receiver antennas 152 and 154. For the purpose of CPT, a potential difference can be applied between the first and second antennas 132 and 134 to generate an electric field (shown as 31B in FIG. 1) to induce a potential across the first and second receiver antennas 152 and 154.

[0174] As depicted in FIG4B, the transmitter resonator 130 includes a first transmitter antenna 132 and a second transmitter antenna 134 separated in the Z direction by a spacer 138.

[0175] The first transmitter antenna 132 may include any suitable antenna capable of generating both a magnetic field 31A and an electric field 31B (alone and / or simultaneously) and having a high self-inductance and a high self-capacitance. For example, the first transmitter antenna may include one of antennas 80, 180, 280 or any other antenna described herein.

[0176] Spacer 138 may comprise any suitable material. For example, spacer 138 may comprise air, a dielectric material, ferrite, or a combination thereof. Spacer 138 may have a dielectric constant selected to change the electric field 31A and / or may have a permeability selected to change the magnetic field 31B. Spacer 138 may comprise a high dielectric constant material to increase the capacitance of transmitter resonator 130. The thickness and planar area of ​​spacer 138 may depend on the thickness and / or planar area of ​​the first and second transmitter antennas 132, 134. In some embodiments, electrical isolation may be desired and a low dielectric constant material may be used for spacer 138 (e.g., for shielding).

[0177] The second transmitter antenna 134 may include any suitable antenna capable of generating both a magnetic field 31A and an electric field 31B (alone and / or simultaneously) and having a high self-inductance and a high self-capacitance. In some embodiments, the second transmitter antenna 134 may be substantially similar to the first transmitter antenna 132 (e.g., the second transmitter antenna 134 may have the same characteristics as any antenna described or depicted herein or otherwise). In some embodiments, the first and second transmitter antennas 132, 134 and the first and second receiver antennas 152, 154 may be different from each other (e.g., the first and second transmitter antennas 132, 134 may be similar to antenna 80, while the first and second receiver antennas 152, 154 may be similar to antenna 180).

[0178] In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be a different size from the XY plane area of ​​the first transmitter antenna 132. In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be smaller than the XY plane area of ​​the first transmitter antenna 132 to ensure coupling between the pairs of antennas. In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be larger than the XY plane area of ​​the first transmitter antenna 132.

[0179] In some embodiments, the second transmitter antenna 134 is substantially complementary to the first antenna 132 in size and / or shape such that the first transmitter antenna 132 and the second transmitter antenna 134 do not substantially overlap in the Z direction. FIG5 depicts a schematic representation of a portion of a transmitter resonator 130 in an XZ plane section, wherein the shapes of the first transmitter antenna 132 and the second transmitter antenna 134 are substantially similar to the first transmitter antenna 180 in FIG2B. As can be seen, portions 132A-1, 132A-2, 132A-3 of the elongated element 132A of the first transmitter antenna 132 overlap in the Z direction with the gaps 134B-1, 134B-2, 134B-3 of the second transmitter antenna 134 (e.g., a line oriented in the Z direction travels through a portion 132A-1 of the elongated element 132A of the first antenna 132 and through the gap 134B-1 of the second antenna 134). Furthermore, portions 134A-1, 134A-2, and 134A-3 of the elongated element 134A of the second transmitter antenna 134 overlap with gaps 132B-1, 132B-2, and 132B-3 of the first transmitter antenna 132 in the Z direction (e.g., a line oriented in the Z direction travels through a portion 134A-1 of the elongated element 134A of the second transmitter antenna 134 through a gap 132B-1 of the second transmitter antenna 134). The complementary shapes of the first transmitter antenna 132 and the second transmitter antenna 134 can reduce parasitic energy losses experienced by the transmitter resonator 130. In some embodiments, the first and second transmitter antennas 132 and 134 may not be completely complementary but may have one or more complementary portions.

[0180] The receiver resonator 150 includes a first receiver antenna 152 and a second receiver antenna 154 separated in the Z direction by a spacer 158. The first receiver antenna 152 may be substantially similar to any of antennas 80, 180, 280 or others described herein. The second receiver antenna 154 may also be substantially similar to any of antennas 80, 180, 280 or others described herein. Like the first and second transmitter antennas 132, 134, the first and second receiver antennas 152, 154 may be complementary (or partially complementary) in size and / or shape.

[0181] In some embodiments, the XY plane area of ​​one of the first and second receiver antennas 152, 154 is different from the XY plane area of ​​one of the first and second transmitter antennas depicted in FIG. 4B in order to adjust the self-inductance or self-capacitance of the receiver resonator 150. For example, in some embodiments, the XY plane area of ​​one of the first and second receiver antennas 152, 154 is larger than the XY plane area of ​​one of the first and second transmitter antennas 132, 134 depicted in FIG. 2A. This difference in XY plane area can improve the ability of the receiver resonator 150 to capture more magnetic field 31A and / or electric field 31B.

[0182] Spacer 158 may include any suitable spacer. Spacer 158 may include the same or similar material as spacer 138 or a different material than spacer 138. Compared to spacer 158, spacer 138 may have a smaller Z-direction dimension to achieve the desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14 and the impedance of the primary side 12. Different compensation networks may be used in both the primary side 12 and the secondary side 14 to accommodate this change in coupling coefficient and impedance.

[0183] Compared to the four-antenna parallel structure depicted in Figure 4C, the stacked configuration in Figure 4B is much more compact in the XY plane. Furthermore, since all antennas can be aligned centrally, this configuration is robust to angular misalignment. Specifically, when the antennas are circular, angular rotation has no effect on the coupling capacitance. However, compared to the four-antenna parallel structure depicted in Figure 4C, the mutual inductance of the stacked configuration in Figure 4B is lower due to the increased cross-coupling capacitance.

[0184] Figure 4C depicts another example of a configuration of antennas 80, 180, and 280. Specifically, Figure 4C depicts a four-antenna parallel (or four-antenna horizontal) WPT system. Each of the transmitter resonator 230 and the receiver resonator 250 includes two antennas. One antenna of the transmitter resonator 230 and one antenna of the receiver resonator 250 together provide a forward path for power, and the other antenna of the transmitter resonator 230 and the other antenna of the receiver resonator 250 together provide a return path for power.

[0185] For the purpose of IPT, a magnetic field is generated by driving a current through the antennas 232 and 234 of the transmitter, which can induce a current in the first and second receiver antennas 252 and 254. For the purpose of CPT, a potential difference can be generated between the first and second antennas 232 and 234 to generate an electric field 31B to induce a potential across the first and second receiver antennas 252 and 254.

[0186] Compared to the transmitter and receiver resonators 130 and 150 shown in Figure 4B, in applications where there is a limitation on the Z-direction dimension of the resonator, a transmitter and receiver resonator 230 and 250 with a horizontally arranged antenna is expected.

[0187] The transmitter resonator 230 includes a first transmitter antenna 232 and a second transmitter antenna 234 separated in the X direction by a spacer 238. By separating the first and second transmitter antennas 232 and 234 in the X direction, parasitic energy loss can be reduced. The first and second transmitter antennas 232 and 234 may be substantially similar to the first and second transmitter antennas 132 and 134, and the spacer 238 may be substantially similar to the spacer 138. Like the transmitter resonator 130, the first transmitter antenna 232 may have an XY plane area that is larger than that of the second transmitter antenna 234 to improve the forward path for power transmission.

[0188] Spacer 238 may include any suitable material. For example, spacer 238 may include air, a dielectric material, ferrite, or a combination thereof. Spacer 238 may have a dielectric constant selected to change the electric field 31A and / or may have a permeability selected to change the magnetic field 31B. Spacer 238 may include a high dielectric constant material to increase the capacitance of transmitter resonator 230. The thickness and planar area of ​​spacer 238 may depend on the thickness and / or planar area of ​​the first and second transmitter antennas 232, 234. In some embodiments, electrical isolation is desirable and a low dielectric constant material may be used for spacer 238 (e.g., for shielding).

[0189] The receiver resonator 250 includes a first receiver antenna 252 and a second receiver antenna 254 separated in the X direction by a spacer 258. By separating the first and second receiver antennas 252, 254 in the X direction, parasitic energy loss can be reduced. The first and second receiver antennas 252, 254 may be substantially similar to the first and second receiver antennas 152, 154, and the spacer 258 may be substantially similar to the spacer 138. Like the receiver resonator 150, the first receiver antenna 252 may have an XY plane area that is larger than the XY plane area of ​​the second receiver antenna 254.

[0190] Spacer 258 may include any suitable spacer. Spacer 258 may include the same or similar material as spacer 238 or a different material than spacer 238. Compared to spacer 258, spacer 238 may have a smaller Z-direction dimension to achieve the desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14 and the impedance of the primary side 12. Different compensation networks may be used in both the primary side 12 and the secondary side 14 to accommodate this change in coupling coefficient and impedance.

[0191] In some embodiments, the XY plane area of ​​spacer 258 may be different from that of spacer 238 in order to change the self-inductance or self-capacitance of transmitter resonator 230 or receiver resonator 250. For example, spacer 238 may have a smaller XY plane area than spacer 258, as depicted.

[0192] Figure 4D depicts another example of a configuration of antennas 80, 180, and 280. Specifically, Figure 4D depicts a six-antenna WPT system combining the stacked configuration of Figure 4B and the parallel configuration of Figure 4C. Each of the transmitter resonator 130 and the receiver resonator 150 includes three antennas. One of the first and second transmitter antennas 332 and 334, and one of the first and second receiver antennas 352 and 354 together provide a forward path for power, and the other of the first and second transmitter antennas 332 and 334, and the other of the first and second receiver antennas 352 and 354 together provide a return path for power. The third transmitter and receiver antennas 336 and 356 operate as auxiliary antennas to increase the equivalent self-capacitance and serve as electric field shielding. In some embodiments, the third transmitter and receiver antennas 336, 356 are passive (e.g., a potential difference is not applied between the third transmitter and receiver antennas 336, 356 and / or current is not driven through the third transmitter and receiver antennas 336, 356). For IPT purposes, by driving a current through one or more of the transmitter antennas 332, 334, 336, a magnetic field is generated that can induce a current in the first receiver antennas 352, 354, 356. For CPT purposes, a voltage can be applied to the first transmitter antenna 332, the second transmitter antenna 334 and / or the third transmitter antenna 336 to generate a potential difference between the first, second and third transmitter antennas 332, 334, 336, thereby generating an electric field 31B.

[0193] The transmitter resonator 330 includes a first transmitter antenna 332 and a second transmitter antenna 334 separated in the X direction by a spacer 338, and a third transmitter antenna 336 separated from the first and second transmitter antennas and the spacer 338 by a second spacer 339. The third transmitter antenna 336 can provide electric field shielding to reduce unwanted electric field escape from the transmitter resonator 330. The third transmitter antenna 336 may contain a ferrite sheet or surface to provide magnetic field shielding to reduce unwanted magnetic field escape from the transmitter resonator 330. The shielding or shaping of the electric or magnetic field can also be made possible by changing the spacer 339.

[0194] The first, second, and third transmitter antennas 332, 334, and 336 may be substantially similar to any of the first and second transmitter antennas 132 and 134. Spacers 338 and 339 may be substantially similar to spacer 138. Like transmitter resonator 130, the first transmitter antenna 332 may have an XY plane area larger than that of the second transmitter antenna 334. The third transmitter antenna 336 may have an XY plane area larger than that of any of the first and second transmitter antennas 334 and 332.

[0195] Spacers 338 and 339 may comprise any suitable material. For example, spacers 338 and 339 may comprise air, a dielectric material, ferrite, or a combination thereof. Spacers 338 and 339 may have a dielectric constant selected to change the electric field 31A and / or may have a permeability selected to change the magnetic field 31B. Spacers 338 and 339 may comprise a high dielectric constant material to increase the capacitance of the transmitter resonator 230. The thickness and planar area of ​​spacers 338 and 339 may depend on the thickness and / or planar area of ​​the first, second, and third transmitter antennas 332, 334, and 336. In some embodiments, electrical isolation is desirable, and a low dielectric constant material may be used for spacers 338 and 339 (e.g., for shielding).

[0196] The receiver resonator 350 includes a first receiver antenna 352 and a second receiver antenna 354 separated in the X direction by a spacer 358, and a third receiver antenna 356 separated from the first and second receiver antennas and the spacer 358 by a second spacer 359. The third receiver antenna 356 can provide electric field shielding to reduce unwanted electric field escapes from the receiver resonator 350. The third receiver antenna 356 may contain a ferrite sheet or surface to provide magnetic field shielding to reduce unwanted magnetic field escapes from the transmitter. Shielding or shaping of the electric or magnetic field can also be made possible by changing the spacer 359. The first, second, and third receiver antennas 352, 354, and 356 may be substantially similar to any of the first and second receiver antennas 152 and 154. The spacers 358 and 359 may be substantially similar to spacer 158. Like the receiver resonator 150, the first receiver antenna 352 may have an XY plane area larger than that of the second receiver antenna 354. The third receiver antenna 356 may have an XY plane area larger than either of the first and second receiver antennas 354 and 352.

[0197] Spacers 358 and 359 may include any suitable spacer. Spacers 358 and 359 may include the same or similar materials as spacers 338 and 339 or different materials. Compared to spacers 358 and 359, spacers 338 and 339 may have a smaller Z-direction dimension to achieve the desired self-capacitance and / or self-inductance. This can effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14 and the impedance of the primary side 12. Different compensation networks can be used in both the primary side 12 and the secondary side 14 to accommodate this change in coupling coefficient and impedance.

[0198] In some embodiments, the XY plane area of ​​spacer 358 may differ from that of spacer 338 to change the self-inductance or self-capacitance of transmitter resonator 330 or receiver resonator 350. For example, spacer 338 may have a smaller X-direction dimension compared to spacer 358. In some embodiments, the Z-direction dimension of spacer 359 may differ from that of spacer 339 to change the self-inductance or self-capacitance of transmitter resonator 330 or receiver resonator 350. For example, spacer 339 may have a smaller Z-direction dimension compared to spacer 359. This can effectively change the coupling coefficient of the link between primary side 12 and secondary side 14 and the impedance of primary side 12. Different compensation networks can be used in both primary side 12 and secondary side 14 to accommodate this change in coupling coefficient and impedance.

[0199] In some embodiments, magnetic shielding may be provided around one or more of the transmitter resonator 30 and the receiver resonator 50. For example, ferrite may be used as magnetic shielding and to reduce unwanted eddy currents in nearby metal objects. Ferrite (or another suitable material) may also be used to isolate the transmitter resonator 30 and / or the receiver resonator 50 from surrounding metal objects and thus may be used to increase the self-inductance of the antenna and / or the mutual inductance of the resonators.

[0200] FIG6 depicts a schematic diagram of a primary side 12 of a transmitter module 20 and a transmitter resonator 30 according to an embodiment of the present invention. The transmitter resonator 30 may include any of the transmitter resonators 30, 130, 230, 330 or others described herein.

[0201] The transmitter module 20 includes a controller 22. The controller 22 is configured to receive various inputs from sensors 24 (e.g., load detector 24A, transmitter power sensor 24B, ambient object detector 24C, and / or distance detector 24D) and output control signals to various components 26 (e.g., oscillator 26A, power amplifier 26B, filter network 26C, matching network 26D, compensation network 26E, and V / I tuner 26F).

[0202] Load detector 24A is configured to detect the presence of a load 70 (shown in FIG. 7) connected to the secondary side 14. Load 70 may be, for example, a battery pack of an electric vehicle (such as an electric bicycle or an electric car) or any other suitable item requiring a power input. Load detector 24A may use a physical sensor (e.g., but not limited to, an optical sensor, a pressure sensor, an infrared sensor, or a proximity sensor) and is suitable for software or firmware implementation. For example, in some embodiments, power (e.g., current and voltage) is measured at point 24E to determine the power drawn by transmitter resonator 30 (e.g., as measured by transmitter power sensor 24B). If the amount of power drawn by transmitter resonator 30 increases above a baseline, load detector 24A may signal the presence of a load 70 to controller 22.

[0203] In other embodiments, load detector 24A can be configured to measure the input impedance of transmitter resonator 30 traversed by transmitter module 20 at point 24E. The presence of a resonant load (including, for example, a secondary side 14 configured to drive load 70) near transmitter resonator 30 will change the input impedance of transmitter resonator 30. This change in impedance provided to controller 22 by load detector 24A can be used by transmitter controller 22 to determine whether a cooperating receiver is near transmitter resonator 30. The impedance changes induced by different receivers in transmitter resonator 30 are so different and so characteristic that controller 22 can not only detect the presence or absence of a receiver near transmitter resonator 30 but also identify the type of receiver (including, for example, (but not limited to) different models of mobile phones or digital tablets).

[0204] The transmitter power sensor 24B can measure the power at point 24E (e.g., measure current and voltage) to determine how much power is drawn by the transmitter resonator 30. This information can be used, for example, by the load detector 24A or to determine whether the desired effective coupling exists between the transmitter resonator 30 and the receiver resonator 50.

[0205] Ambient Object Detector (SOD) 24C is configured to determine whether an object (e.g., a living being (such as a human or an animal) or an inanimate object (such as a piece of metal or otherwise)) is near the transmitter resonator 30. The SOD 24C may use a physical sensor (e.g., but not limited to, an optical sensor, a pressure sensor, an infrared sensor, a proximity sensor, RADAR, or LIDAR) or be implemented using software or firmware. For example, if the power drawn by the transmitter resonator 30 (e.g., measured by the transmitter power sensor 24B) decreases during IPT, the SOD software may determine that a piece of metal (or any electrical conductor) is near the transmitter resonator 30 or receiver resonator 50, and the SOD may provide a signal indicating this presence to the controller 22. In some embodiments, if a metallic object is detected near the transmitter resonator 30 or receiver resonator 50, the controller 22 may cause the transmitter module 20 to increase a proportion of the power delivered by CPT. In the absence of a creature such as that detected by SOD 24C, the controller 22 can be configured to increase the power fed to the transmitter resonator 30 (e.g., above an adjusted level in the presence of a creature), or in the presence of a creature such as that detected by SOD 24C, the controller 22 can be configured to reduce the power fed to the transmitter resonator 30 to below an adjusted level.

[0206] The distance detector 24D is configured to determine one of the distances between the transmitter resonator 30 and the receiver resonator 50. The distance detector 24D can use a physical sensor (e.g., but not limited to, an optical sensor, an ultrasonic sensor, an infrared sensor, a proximity sensor, a RADAR, or a LIDAR) or be implemented using software or firmware. For example, the distance detector 24D can be configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50 based on changes in transmitted power, such as those measured by the transmitter power sensor 24B.

[0207] In one embodiment, one or more temperature sensors may monitor the temperature at the transmitter resonator 30 or receiver resonator 50. If the temperature exceeds a predetermined limit, the controller 22 may cause the transmitter module 20 to reduce the proportion of power delivered by the IPT, reduce the overall power fed to the transmitter resonator 30, or cut off the power supply to the transmitter resonator 30 to prevent a fire hazard or heat dissipation.

[0208] The oscillator 26A can be configured to control the frequency band and / or bandwidth and / or operating time cycle (phase) of the current delivered to the transmitter resonator 30 in response to a signal from the controller 22 (e.g., 5% to 50%).

[0209] Power amplifier 26B can be used to convert DC power to AC power. Power amplifier 26B can be used to adjust the power supplied to transmitter resonator 30 in response to a signal from controller 22. Specifically, controller 22 can send a signal to power amplifier 26B to adjust the reflection coefficient of power amplifier 26B. In some embodiments, controller 22 can send a signal to power amplifier 26B to turn off (or sleep) when load detector 24A does not detect a load or to turn on when load detector 24A detects a load.

[0210] Power amplifier 26B may include a switch-mode power amplifier (in single-ended mode or differential mode) that can be configured to receive a square (sine) wave from self-oscillator 26A and generate a sine wave with a specific frequency desired to drive transmitter resonator 30. Figure 8 is a schematic diagram of an exemplary power amplifier 26B that can be used in transmitter 30. Power amplifier 26B may be a differential switch-mode amplifier. Power amplifier 26B has three inputs: two input signals that drive active devices (transistors) 127C and 127D using a frequency set at the resonant frequency, and a DC voltage source 127E for controlling the output power of the active devices and the operating region.

[0211] Different load terminations are used to improve performance (e.g., output power, power conversion efficiency) and reduce unnecessary harmonic levels. Specifically, the third harmonic termination 127F is positioned in the series branch to shape the voltage waveform at the drain node 127G. The second harmonic termination 127H is positioned in the parallel branch to shape the voltage waveform at the drain node 127G. The first harmonic termination 127I is positioned in the series branch to shape the voltage waveform at the drain node 127G. The effect of the third harmonic termination can be considered in the second and first harmonic terminations 127H and 127I. The effect of the second harmonic termination can be considered in the first harmonic termination 127I. For the differential configuration of the power amplifier 26B, an AC load 127J (which receives the output power) is placed in series. The charging rate AC load 127J can vary depending on the alignment and position of the transmitter resonator 30, the receiver resonator 50, and / or their respective resonators. The power amplifier 26B can be configured to generate sufficient power to the transmitter resonator 30 so that the E field or the H field or any combination of the E field and the H field can be generated by the transmitter resonator 30 and captured by the receiver resonator 50.

[0212] Amplifier 26B may include two phase shifters 127L in a differential configuration (but only one phase shifter is in a single-ended configuration). Phase shifter 127L adjusts the appropriate phase difference between the AC signal overload 127J and the gate signals of transistors 127C and 127D. The phase difference between the gate signals and the AC signal overload 127J can change the performance of the power amplifier (e.g., the power conversion efficiency and operating range of the transistors). It can also change the output impedance of transistors 127C and 127D and / or the optimal AC load 127J of power amplifier 26B.

[0213] Amplifier 26B may include two level shifters 127K in a differential configuration (but only one level shifter is in a single-ended configuration). Level shifters 127K can adjust the appropriate amplitude of the gate signals of transistors 127C and 127D. The amplitude level at the gate signals can change the amplifier's performance (e.g., the power conversion efficiency and operating range of the transistors).

[0214] Amplifier 26B is reconfigurable to function as a rectifier, particularly as a self-synchronizing rectifier. As part of this reconfiguration, the integrated phase shifter 127L and the integrated level shifter 127K can be adjusted to allow amplifier 26B to function as a rectifier 26B based on the inherent amplification and switching functions of transistors 127C and 127D. This reconfigurability of amplifier 26B between operating as an amplifier and operating as a rectifier allows transmitter module 20 to be controllably reconfigured between a transmitter mode and a receiver mode, respectively. Reconfiguration can occur under command from controller 22. When amplifier 26B is reconfigured from an amplifier to a rectifier, AC load 127J changes to an AC source 127J. Correspondingly, when amplifier 26B is reconfigured from an amplifier to a rectifier, DC source 127E is reconfigured to a DC load. Once we have described the secondary side 14 and its receiver module, we will now deal with the application of the transmitter module 20 in its receiver mode, both of which are shown in more detail in Figure 7.

[0215] The filter network 26C can respond to a signal provided by the controller 22 to the frequency response (such as bandwidth, cutoff frequency, 3dB frequency, gain) of the transmitter resonator 30. The filter network can be configured to adjust the shape of the waveform of the power in the transmitter module 20 to increase the efficiency of the transmitter module 20.

[0216] The matching network 26D can be configured to adjust the impedance to match the output of the power amplifier 26B with the transmitter resonator 30.

[0217] A compensation network 26E may be provided to drive the transmitter resonator 30 at a desired resonant frequency (e.g., the resonant frequency of the receiver resonator) to increase throughput, reduce heat generation, and improve power transmission efficiency. The compensation network 26E may include one or more capacitors for increasing capacitance and one or more inductors for increasing inductance. The compensation network 26E can be configured to increase (and / or decrease) capacitance and increase (and / or decrease) inductance as needed. When the transmission mode ratio is 100% CPT, the compensation network 26E can function similarly to any known CPT compensation network (e.g., compensation network 26E can be used to increase inductance). Similarly, when the transmission mode ratio is 100% IPT, the compensation network 26E can function similarly to any known IPT compensation network (e.g., compensation network 26E can be used to increase capacitance). However, when the transmission mode ratio is a combination of partial CPT and partial IPT, less compensation may be required. This is because the capacitance of the transmitter resonator 30 will naturally compensate for the inductance of the transmitter resonator 30, and the inductance of the transmitter resonator 30 will naturally compensate for the capacitance of the transmitter resonator 30. For example, at approximately 50% IPT and 50% CPT (e.g., a transmission mode ratio equal to one), a compensation network may be completely unnecessary or its use may be substantially limited, thereby increasing the efficiency of the WPT system 10.

[0218] As another example, between approximately 40% to 60% IPT and 40% to 60% CPT, a compensation network may be completely unnecessary or its use may be substantially limited, thereby increasing the efficiency of the WPT system 10. For this reason, compared to CPT WPT systems and / or pure IPT WPT systems that require significant compensation, the compensation network 26E may include fewer or smaller inductors and / or capacitors. In some embodiments, if the capacitance of the transmitter resonator 30 is sufficiently low, additional compensation may be provided by the compensation network 26E. Similarly, if the inductance of the transmitter resonator 30 is sufficiently low, additional compensation may be provided by the compensation network 26E. The controller 22 may signal the amount and type of compensation required to the compensation network 26E based on, for example, the transmission mode ratio, one of the distances between the transmitter resonator 30 and the receiver resonator 50, the amount of power drawn by the transmitter resonator 30, power transmission efficiency, etc.

[0219] In some embodiments, the amount compensated by the compensation network 26E (e.g., an increase in capacitance or inductance) is proportional to the absolute value of the difference between the transmission mode ratio and one. For example, if the transmission mode ratio is greater than one, the compensation network 26E can be used to increase the inductance, and the amount of increase in inductance can be increased when the transmission mode ratio increases by more than one. Similarly, if the transmission mode ratio is less than one, the compensation network 26E can be used to increase the capacitance, and the increase in capacitance can be increased when the transmission mode ratio decreases by more than one.

[0220] In some embodiments, the compensation network 26E can be configured to use information modulation to provide a signal to the transmitter resonator 30 and can thereby be used as a source transmission modulator. Information used to modulate the signal provided to the transmitter resonator 30 can be provided to the compensation network 26E via the controller 22. The information may include control data assigned to the controller 42 of the receiver module 40 via the receiver resonator 50. The controller 42 is described in more detail below with reference to FIG7. In other embodiments, the power amplifier 26B can be used as a source transmission modulator. In yet another embodiment, the oscillator 26A can be used as a source transmission modulator. The modulation employed by the selected source transmission modulator can be any of amplitude modulation, frequency modulation, and phase modulation. The information can be modulated digitally or analogically to the signal provided to the transmitter resonator 30. The information can be modulated by the source transmission modulator to the resonant frequency of the power signal provided to the transmitter resonator 30. In other embodiments, the information may be modulated to a frequency different from the frequency of power transmission. In other embodiments, the information may be modulated to a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 30. In yet another embodiment, the resonant frequency of the power signal provided to the transmitter resonator 30 may be a harmonic of the frequency of the signal to which the information is modulated. The V / I tuner 26F, described in more detail below, may be configured to transmit information signals to the transmitter resonator 30 and thereby be transparent with respect to the transmitted information. Information transmitted in the manner described herein may include (but is not limited to) the operating mode of module 20, the number and type of receivers 40, ambient object sensor information, and load status monitoring information (including, for example, battery charge status, load voltage, and load current).

[0221] An embodiment of the V / I tuner 26F is shown in more detail in Figure 10. The input signal of the V / I tuner 26F received by the self-matching network 26E (in Figure 6) is split by a splitter 262 to have two mutually asymmetrical paths 261A and 261B for the input signal. A first phase shifter 264A and a second phase shifter 264B generate a phase difference between the input voltage and the input current of the transmitter resonator 30 (in Figure 6). The first phase shifter 264A is controlled by the controller 22 (in Figure 6) via a first phase splitter control line 263A, and the second phase shifter 264B is controlled by the controller 22 (see Figure 6) via a second phase splitter control line 263B. The first and second active switches 266A and 266B receive signals from the first and second phase shifters 264A and 264B, respectively, and are controlled by the controller 22 via first and second active switch control lines 265A and 265B, respectively. The first and second active switches 266A and 266B are used to adjust the hypothetical portions of the signals received from the first and second phase shifters 264A and 264B, respectively. Passive signal shaping networks 268A and 268B receive the adjusted signals from the first and second active switches 266A and 266B, respectively. Passive signal shaping networks 268A and 268B are used to fine-tune the signals received from the first and second active switches 266A and 266B, respectively, and specifically, to reduce any harmonics in the signals before passing them to the combiner 269. Signals provided along two mutually asymmetrical paths 261A and 261B are combined by the combiner 269 and provided to the transmitter resonator 30. In other embodiments, the first and second phase shifters 264A and 264B can be combined into a single phase shifter that receives the input signal to the V / I tuner 26F, and the combined phase shifter can have two separate outputs that function as active switches 266A and 266B.

[0222] The V / I tuner 26F adjusts the transmission mode ratio by responding to the signal from the controller 22 to adjust the phase difference between the input current and the input voltage of the transmitter resonator 30. The real part of the impedance seen by the transmitter module 20 is adjusted by phase shifters 264A and 264B, and its imaginary part can be adjusted by switches 266A and 266B. For example, a 90-degree phase shift every 3 milliseconds in 10 milliseconds can result in 30% magnetic power transfer and 70% power transfer.

[0223] The V / I tuner 26F can be configured to adjust the current passing through each transmitter antenna (e.g., the first and second transmitter antennas 32, 132, 232, 332, 134, 234, 334 or the third transmitter antenna 336) and the potential applied to each transmitter antenna (e.g., the first and second transmitter antennas 32, 132, 232, 332, 134, 234, 334 or the third transmitter antenna 336).

[0224] If current is induced to flow through both the first and second transmitter antennas 132 and 134, they will each generate a magnetic field 31A for the purpose of IPT. If the current delivered to the second transmitter antenna 134 is reduced compared to the current delivered to the first transmitter antenna 132, a potential difference and an electric field 31B will be generated between the first and second transmitter antennas 132 and 134 for the purpose of CPT. To modulate between CPT and IPT, the current delivered to the second antenna 134 can be modulated (e.g., less IPT will occur when less current is allowed to flow through the second antenna 134, and more CPT will occur when more current is allowed to flow through the second antenna). For example, when it is desired to transmit power via IPT, the I / V tuner 26F can be configured to act as a short circuit of a series LC resonator that connects the first and second transmitter antennas together to generate a current flow therein. Conversely, when power is desired to be transmitted via CPT, the I / V tuner 26F can be configured to function as an open circuit that dumps current, thereby generating a potential difference between the first and second transmitter antennas. The I / V tuner 26F can thus be configured to control whether the first and second transmitter antennas 132 and 134 are effectively connected in series or in parallel.

[0225] Alternatively, when the first and second transmitter antennas 132 and 134 are connected in parallel, the first and second transmitter antennas 132 and 134 can be floated for CPT purposes to generate an electric field 31B, without substantially generating a magnetic field 31A. To change the transmission mode ratio (e.g., modulation between CPT and IPT), the I / V tuner 26F can be configured (by a multiplexer of the I / V tuner 26F or the like) to alternate between (1) floating the first and second transmitter antennas 132 and 134 to generate CPT and (2) driving current through the first and second transmitter antennas 132 and 134 to generate IPT. The alternation can be implemented within milliseconds or at a frequency between 10 Hz and 10 kHz. When more time is allocated to the floating first and second transmitter antennas 132, 134, the transmission mode will be biased towards more CPT, and when more time is allocated to the drive current passing through the first and second transmitter antennas 132, 134, the transmission mode will be biased towards more IPT.

[0226] In some embodiments, element 26 may be a discrete element in transmitter module 20, while in other embodiments, one or more of element 26 may be part of an integrated circuit design.

[0227] FIG7 is a schematic depiction of a load 70 and a secondary side 14 (shown in FIG1) including a receiver resonator 50 and a receiver module 40 according to one embodiment of the present invention.

[0228] The receiver resonator 50 may include any of receiver resonators 50, 150, 250, 350 or others described herein. The receiver resonator 50 may be configured to capture power using a frequency (such as (e.g., but not limited to) between 1 MHz and 1 GHz) set by one of the oscillation signals in the transmitter module 20.In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is approximately 1 MHz to approximately 100 MHz, approximately 1 MHz to approximately 200 MHz, approximately 1 MHz to approximately 300 MHz, approximately 1 MHz to approximately 400 MHz, approximately 1 MHz to approximately 500 MHz, approximately 1 MHz to approximately 600 MHz, approximately 1 MHz to approximately 700 MHz, approximately 1 MHz to approximately 800 MHz, approximately 1 MHz to approximately 900 MHz, approximately 1 MHz to approximately 1 GHz, approximately 100 MHz to approximately 200 MHz, approximately 100 MHz to approximately 300 MHz, approximately 100 MHz to approximately 400 MHz, approximately 100 MHz to approximately 500 MHz, approximately 100 MHz to approximately 600 MHz, approximately 100 MHz to approximately 700 MHz, approximately 100 MHz to approximately 800 MHz, approximately 100 MHz to approximately 900 MHz, approximately 100 MHz to approximately 1 GHz, approximately 200 MHz to approximately 100 MHz, approximately 1 ... MHz to 300 MHz, approximately 200 MHz to 400 MHz, approximately 200 MHz to 500 MHz, approximately 200 MHz to 600 MHz, approximately 200 MHz to 700 MHz, approximately 200 MHz to 800 MHz, approximately 200 MHz to 900 MHz, approximately 200 MHz to 1 GHz, approximately 300 MHz to 400 MHz, approximately 300 MHz to 500 MHz, approximately 300 MHz to 600 MHz, approximately 300 MHz to 700 MHz, approximately 300 MHz to 800 MHz, approximately 300 MHz to 900 MHz, approximately 300 MHz to 1 GHz, approximately 400 MHz to 500 MHz, approximately 400 MHz to 600 MHz, approximately 400 MHz to 700 MHz, approximately 400 MHz to 800 MHz, approximately 4 ... MHz to 900 MHz, about 400 MHz to 1 GHz, about 500 MHz to 600 MHz, about 500 MHz to 700 MHz, about 500 MHz to 800 MHz, about 500 MHz to 900 MHz, about 500 MHz to 1 GHz, about 600 MHz to 700 MHz, about 600 MHz to 800 MHz, about 600 MHz to 900 MHz, about 600 MHz to 1 GHz, about 700 MHz to 800 MHz, about 700 MHz to 900 MHz, about 700 MHz to 1 GHz, about 800 MHz to 900 MHz, about 800 MHz to 1 GHz, or about 900 MHz to 1 GHz.In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is approximately 1 MHz, approximately 100 MHz, approximately 200 MHz, approximately 300 MHz, approximately 400 MHz, approximately 500 MHz, approximately 600 MHz, approximately 700 MHz, approximately 800 MHz, approximately 900 MHz, or approximately 1 GHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at least approximately 1 MHz, approximately 100 MHz, approximately 200 MHz, approximately 300 MHz, approximately 400 MHz, approximately 500 MHz, approximately 600 MHz, approximately 700 MHz, approximately 800 MHz, or approximately 900 MHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is up to about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz or about 1 GHz.

[0229] For some applications, frequencies in the Industrial, Scientific, and Medical (ISM) band may be preferred. For the purposes of this invention, the ISM band is understood to be 6.765 MHz to 6.795 MHz; 13.553 MHz to 13.567 MHz; 26.957 MHz to 27.283 MHz; 40.66 MHz to 40.70 MHz; 83.996 MHz to 84.004 MHz; 167.992 MHz to 168.008 MHz; 433.05 MHz to 434.79 MHz; and 886 MHz to 906 MHz. For other applications, frequencies in the application band are officially reserved as preferred, such as (but not limited to) police communications or military bands. The receiver resonator 50 can be configured to capture electricity from the magnetic field 31A or the electric field 31B or any combination of the two fields at that frequency.

[0230] The receiver module 40 includes a controller 42. The controller 42 is configured to receive various inputs (e.g., receiver power sensor 44A and load detector 44B) from the sensor 44 and output control signals to various components 46 (e.g., compensation network 46A, matching network 46B, rectifier 46D, filter 46C and load manager 46E).

[0231] The receiver power sensor 44A can measure the power at point 44C (e.g., measure current and voltage) to determine how much power is received by the receiver resonator 50.

[0232] Load detector 44B is configured to detect the presence of load 70. Load detector 44B may use a physical sensor (e.g., but not limited to, an optical sensor, a pressure sensor, an infrared sensor, or a proximity sensor) or be implemented using software or firmware. For example, in some embodiments, load detector 44B measures current and voltage at, for example, point 44D to determine the power received by load 50. If the amount of power measured at point 44D increases above a baseline, load detector 44B may signal the presence of load 70 to controller 42.

[0233] The compensation network 46A can be configured to maintain a desired resonant frequency of the receiver resonator 50 in response to a signal from the controller 42, thereby improving the efficiency of power transmission from the transmitter resonator 30 to the receiver resonator 50. The compensation network 46A can be the compensation network 26E of the transmitter module 20 and can function substantially similarly to the compensation network 26E of the transmitter module 20.

[0234] The matching network 26D can be configured to adjust the input impedance of one of the rectifiers 46D to match the required impedance of one of the resonators 30 to achieve maximum power transmission.

[0235] The rectifier 46D can be configured to convert AC power received by the receiver antenna 50 into DC power to supply to the load 70.

[0236] Figure 46C can be configured to shape the waveform of the power output from the self-rectifier 46D according to a signal from the controller 42 in order to improve the overall power efficiency of the receiver module 40.

[0237] The load manager 46E can be configured to provide the load 70 with suitable voltage and current and / or draw maximum power from the rectifier 46D by adjusting its input impedance (e.g., the output impedance of the rectifier 46D).

[0238] In some embodiments, the load manager 46E or another component may be configured to communicate (wirelessly or wired) with an external device (e.g., load 70) to provide appropriate information for data analysis. This information may include (e.g., but not limited to) the presence of load 70, a charging level of load 70, a charging rate of load 70, the state of load 70, a current voltage, capacitance, and / or the remaining time to charge load 70. The load manager 46E may use this information (or relay this information to controller 42 or controller 22) to adjust (e.g.) the transfer mode ratio to achieve optimal energy transfer between the primary side 12 and the secondary side 14. The load manager 46E may also provide this information to a user via a display. This display may be built into one or more of the primary side 12 and the secondary side 14 or may be accessed via software on a mobile device (such as (e.g., an application on a mobile phone or tablet computer that communicates wirelessly (or wiredly) with the load manager 46E or controller 22 or controller 42).

[0239] In some embodiments, component 46 is a discrete element in receiver module 40, while in other embodiments, one or more of component 46 is part of an integrated circuit design.

[0240] In some embodiments, a primary side 12 may include a plurality of transmitter resonators 30 and / or a secondary side 14 may include a plurality of receiver resonators 50. In these embodiments, each of the transmitter resonators 30 and / or receiver resonators 50 may be controlled in a similar manner. In other embodiments, each of the transmitter resonators 30 and / or receiver resonators 50 may be controlled individually. For example, in some embodiments, the primary side 12 may rely more heavily on transmitter resonators 30 that experience less interference (e.g., due to a nearby metal object) and are not near a living organism or transmit power more efficiently, and / or similarly, the secondary side 14 may rely more heavily on receiver resonators 50 that experience less interference (e.g., due to a nearby metal object) and are not near a living organism or receive power more efficiently. This control may be provided or facilitated by, for example, communication between transmitter module 20 and receiver module 40 and / or the like.

[0241] FIG9 is a schematic depiction of a rectifier 46D having an integrated phase shifter. In some embodiments, the rectifier 46D includes a discrete phase shifter.

[0242] The rectifier 46D may be a switching-mode self-synchronous rectifier (in single-ended mode or a differential mode) configured to receive a sinusoidal wave (e.g., AC power) from the receiver resonator 50 at a specific resonant frequency. The rectifier 46D may be a differential switching-mode self-synchronous rectifier. The rectifier 46D may capture sufficient power from the receiver resonator 50 such that the E field, the H field, or any combination of the E field and the H field can be captured by the receiver resonator 50.

[0243] The rectifier 46D has an input 147A (e.g., AC power) that drives an active device 147B (e.g., a transistor) at a frequency set at the resonant frequency, and an output 147D (e.g., DC voltage) across a DC load (for controlling the output power, input impedance, and operating range of the active device). In this design, different load terminations are used to improve performance (e.g., output power and power conversion efficiency). The third harmonic termination 147D is positioned in the series branch to shape the voltage waveform at the drain node 147E. The second harmonic termination 147F is positioned in the parallel branch to shape the voltage waveform at the drain node 147E. The first harmonic termination 147G is positioned in the series branch to shape the voltage waveform at the drain node 147E. The effect of the third harmonic termination can be considered in the second and first harmonic terminations. The effect of the second harmonic termination can be considered in the first harmonic termination.

[0244] For differential mode, AC source 147A is placed in series. AC source 147A can vary depending on the power received by receiver resonator 50 and the alignment and position of receiver resonator 50 relative to transmitter resonator 30. DC load 147C can be a single-ended load.

[0245] The rectifier 46D may include two phase shifters 147H in a differential configuration (but only one phase shifter is in a single-ended configuration). The phase shifter 147H adjusts the appropriate phase difference between the AC source and the gate signal of the transistor 147B. The phase difference between the gate signal and the AC source 147A can alter the efficiency of the synchronous rectifier (e.g., the power conversion efficiency and operating range of the transistor). It can also alter the input impedance of the synchronous rectifier 46D and / or the optimal DC load 147C of the rectifier 46D.

[0246] The rectifier 46D may include two level shifters 147I in a differential configuration (but only one level shifter is in a single-ended configuration). The level shifter 147I can adjust the appropriate amplitude of the gate signal of the transistor 147B. The amplitude level at the gate signal can change the efficiency of the synchronous rectifier (e.g., the power conversion efficiency and operating range of the transistor).

[0247] The rectifier 46D is reconfigurable to function as an amplifier. As part of this reconfiguration, the integrated phase shifter 147H and the integrated level shifter 147I can be adjusted to allow the rectifier 46D to function as an amplifier based on the inherent amplification and switching functions of the transistor 147B. This reconfigurability of the rectifier 46D between operating as a rectifier and operating as an amplifier allows the receiver module 40 to be controllably reconfigured between a receiver mode and a transmitter mode, respectively. The reconfiguration can occur under a command from the controller 42. When the rectifier 46D is reconfigured from a rectifier to an amplifier, the AC source 147A changes to an AC load 147A. Correspondingly, when the rectifier 46D is reconfigured from a rectifier to an amplifier, the DC load 147C is reconfigured to a DC source.

[0248] In some embodiments, when the receiver module 40 is in transmitter mode, the compensation network 46A can be configured to use information modulation to provide a signal to the resonator 50 and can thereby function as a source transmission modulator. Information used to modulate the signal provided to the resonator 50 can be provided to the compensation network 46A via the controller 42. The information may include control data assigned to the controller 22 of the transmitter module 20 via the resonator 30. In some embodiments, when the receiver module 40 is in transmitter mode and the rectifier 46D is configured as an amplifier, the rectifier 46D can function as a modulator for the module 40. The modulation employed can be any of amplitude modulation, frequency modulation, phase modulation, and combinations thereof. The information can be modulated digitally or analogously to the signal provided to the transmitter resonator 50. The information can be modulated by the source transmission modulator to the resonant frequency of the power signal provided to the transmitter resonator 50. In other embodiments, the information may be modulated to a frequency different from the frequency of power transmission. In other embodiments, the information may be modulated to a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 50. In yet another embodiment, the resonant frequency of the power signal provided to the transmitter resonator 50 may be a harmonic of the frequency of the signal to which the information is modulated. The information transmitted in the manner described herein may include (e.g., but not limited to) the presence of load 70, a charging level of load 70, power transmission efficiency, a charging rate of load 70, the state of load 70, a current voltage, charging capacity, and / or the remaining time for charging load 70.

[0249] Having described above how modules 20 and 40 can be reconfigured between transmitter and receiver modes, and how signals from both modules 20 and 40 can be modulated, it is clear that system 10 of FIG1 can be used as a full-duplex transmit-receive system for transmitting information in both directions via resonators 30 and 50. System 10 of FIG1 may include a further secondary side similar to secondary side 14 of FIG1 and FIG7. When an additional secondary side is present, the configuration described above allows communication of information among the various secondary sides.

[0250] In some embodiments, the primary side 12 and the secondary side 14 may communicate via Bluetooth (e.g., 2.4 GHz) or a signal frequency similar to GPS (e.g., 10 GHz). In some embodiments, there may be an additional unit capable of independently collecting data and transmitting data back and forth between the primary side 12 and / or the secondary side 14. In some embodiments, WiFi may be used to upload data from the primary side 12 and / or the secondary side 14 to an online portal (e.g., a website or mobile application associated with the primary side 12 and / or the secondary side 14).

[0251] In some embodiments, it is desirable to transfer power between two receiver modules 40 (e.g., peer-to-peer power transfer). For example, if a first electric bicycle having a first receiver has a depleted or low-power battery pack and a second electric bicycle having a second receiver and at least a partially rechargeable battery pack is nearby, it is desirable to transfer power from the second electric bicycle to the first electric bicycle. This scenario may be suitable, for example, when no transmitter is nearby. Reconfiguring the facilities of at least one of the two receiver modules 40 involved in a transmitter module makes this peer-to-peer power transfer feasible. Generally speaking, it makes it possible to transfer power among a plurality of secondary sides 14.

[0252] In other embodiments, it may be necessary to transmit power in the opposite direction (i.e., from the load side to the source side in Figures 1, 6, and 7) at certain times. The ability of modules 20 and 40 to reconfigure between operation in transmitter mode and receiver mode allows for this transmission of power from module 40 to module 20 in the "opposite" direction. Therefore, the system allows bidirectional power transmission. Given that devices 26B and 46D of Figures 8 and 9 can be reconfigured to function as amplifiers or rectifiers, these devices may be collectively referred to as "differential self-synchronizing RF power amplifiers / rectifiers". Given the bidirectional nature of power transmission, both transmitter resonator 30 and receiver resonator 50 can be described as "transmitter-receiver resonators" and both modulators 20 and 40 can be referred to as "power transmission-receive modules". Such configurations can be used in electric vehicles in which kinetic energy is converted during braking and needs to be transmitted to the battery pack. Other systems, conditions, and configurations that utilize this change of direction for power transmission include (for example, but not limited to) several mobile phones that may have different levels of remaining battery charge and that can use this configuration to at least partially recharge each other. More generally, when neither a transmitting system nor a receiving system has a permanent energy source (e.g., the power grid), bidirectional functionality can be employed to transmit energy in either direction.

[0253] In a further embodiment of the description with respect to FIG31, a near-field radio frequency method

[2200] for transmitting power via a power signal at a power signal frequency is provided, the method comprising: providing

[2210] a dual-mode resonant near-field radio frequency power transmission system comprising a plurality of power transmission-receive modules, wherein each of the plurality of power transmission-receive modules is in wire communication with a transmitter-receiver resonator arranged to exchange power with at least another of the plurality of power transmission-receive modules; and operating

[2220] the power transmission system to simultaneously perform capacitive power transmission and inductive power transmission according to an adjustable transmission mode ratio.

[0254] The power transmission system may include providing one of a plurality of power transmission-receiving modules having a power signal tuner module and operating

[2420] the power transmission system may include changing the transmission mode ratio by adjusting the power signal tuner module.

[0255] Providing

[2210] a power transmission system may include at least one power transmission-receive module among a plurality of power transmission-receive modules that is wired to an associated transmitter-receiver resonator and has a modulator, and operating

[2220] the power transmission system may include: exchanging a radio frequency signal between the associated transmitter-receiver resonator and a transmitter-receiver resonator that is wired to at least another of the plurality of power transmission-receive modules; and modulating information onto the exchanged radio frequency signal. When a power load is present at one of the outputs of one of the plurality of power transmission-receive modules, the information modulated on the exchanged signal may include (e.g., but not limited to) one or more of the following: the presence of a power load, a charging level of a power load, a power transmission efficiency, a charging rate of a power load, a state of a power load, the presence of a voltage on the power load, a charging capacity of a power load, and a remaining charging time for the power load.

[0256] Information can be modulated onto a switched radio frequency signal by amplitude modulation, frequency modulation, or phase modulation. Modulating information onto a switched radio frequency signal may include modulating digital information or analog information onto a switched radio frequency signal.

[0257] Modulating information onto a switched radio frequency signal may include modulating the information onto a power signal. Modulating information onto a switched radio frequency signal may include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating information onto a switched radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating information onto a switched radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

[0258] Modulating information onto a switched radio frequency signal may include modulating the reflection characteristics of one of the associated wire-connected transmitter-receiver resonators according to the information to apply the information to a signal reflected by the wire-connected transmitter-receiver resonator. Modulating information onto a switched radio frequency signal may include modulating the signal provided to one of the associated transmitter-receiver resonators according to the information.

[0259] The method

[2200] may include operating a power signal tuner module of a first of a plurality of power transmission-reception modules to modulate information onto a switched radio frequency signal. Each of the power transmission-reception modules provided may include a compensation network and the compensation network may include a modulator, thereby allowing the compensation network to operate to modulate information onto a switched radio frequency signal. At least one of the power transmission-reception modules may include providing a signal at a power signal frequency to a radio frequency oscillator of at least one power transmission-reception module, and the radio frequency oscillator may include a modulator, thereby allowing information to be modulated onto a switched radio frequency signal in the oscillator.

[0260] Each of the plurality of provided power transmission-receive modules can be reconfigured between a power transmitter mode and a power receiver mode; and the method may further include reconfiguring at least two of the plurality of power transmission-receive modules between a power transmitter mode and a power receiver mode to reverse one direction of power transmission between at least two transmission-receive modules. Each of the provided power transmission-receive modules may include a differential self-synchronous radio frequency power amplifier / rectifier capable of reconfiguring between an amplifier state and a rectifier state corresponding to a power transmitter mode and a power receiver mode of the power transmission-receive module, respectively; and the method may include reconfiguring the differential self-synchronous radio frequency power amplifier / rectifier of at least two transmission-receive modules between the amplifier state and the rectifier state. Each differential self-synchronizing RF power amplifier / rectifier may include a phase shifter that can be adjusted to reconfigure the differential self-synchronizing RF power amplifier / rectifier between amplifier and rectifier states; and the method may include adjusting one of the phase shifters of each of the differential self-synchronizing RF power amplifiers / rectifiers of at least two transmit-receive modules.

[0261] The WPT system 10, which includes the transmitters and / or receivers described herein, can be integrated into various applications (such as, but not limited to, electric vehicles, electric boats, electric aircraft, electric trucks, electric bicycles, electric motorcycles, electric skateboards, etc.). An exemplary, non-limiting application is a shared bicycle fleet, in which various connection stations integrating one or more transmitters (e.g., primary side 12) and including receivers (e.g., secondary side 14) and battery packs (as load 70) are provided, and electric bicycles can be charged at the connection stations.

[0262] In some applications, the primary side 12 or the secondary side 14 can be configured to transmit power using other systems not described herein and the transmission mode ratio from CPT to IPT can be adjusted to provide compatibility with other CPT and / or IPT systems, even if they are not specifically designed to work with the power transmission systems described herein.

[0263] Although several exemplary models and embodiments have been discussed above, those skilled in the art will recognize certain modifications, arrangements, additions, and sub-combinations thereof. Therefore, the appended claims and the technical solutions described below are interpreted to include all such modifications, arrangements, additions, and sub-combinations, as consistent with the broadest interpretation of the specification as a whole.

[0264] In a first state, each of the systems described above and depicted in Figures 1 to 10 forms a dual-mode near-field resonant wireless power transmission system 10 configured to simultaneously perform capacitive and inductive power transmission at a variable resonant power signal oscillation frequency according to an adjustable transmission mode ratio. The system 10 includes: a transmitter subsystem 12, which includes transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336, and a power signal tuner module 26F. Module 26F is configured to adjust the transmission mode ratio by adjusting one of the power signals provided by tuner module 26F to transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336; and a receiver subsystem 14, which includes receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356 configured to receive power from transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 at the transmission mode ratio.

[0265] The tuner module 26F can be configured to adjust the power signal by adjusting a phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336. The transmitter subsystem 12 may further include a controller 22 and at least one sensor 24, wherein the controller 22 is configured to receive sensor information from at least one sensor 24 and to automatically provide a tuning command to the tuner module 26F based on the sensor information; and the tuner module 26F is configured to adjust the phase difference between the current and voltage of the power signal provided to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 according to the tuning command.

[0266] System 10 resonates at a resonant frequency that varies freely within a predetermined frequency band based on the degree of coupling between transmitter subsystem 12 and receiver subsystem 14. The predetermined frequency band may be (e.g., but not limited to) an officially designated and reserved Industrial, Scientific, and Medical (ISM) band or a band dedicated to a specific user. The quality factor (Q) of system 10 can be reduced to a degree that allows the power signal oscillation frequency to vary within the opposite limit of the predetermined frequency band. This reduction in Q allows system 10 to employ any of several different resonant frequencies within the predetermined frequency band during power transmission. The coupling between transmitter subsystem 12 and receiver subsystem 14, and the associated absorption of power by resonant receiver subsystem 14, ensure that less electromagnetic radiation is emitted into the far field when system 10 is in operation. The configuration described herein with reference to Figures 1 through 10, and the frequency states immediately preceding them, make system 10 a two-mode near-field resonant wireless power transmission system. It should be noted that in the wireless power transmission system 10, power is transmitted from the primary subsystem to the secondary subsystem via capacitive or inductive coupling or both, and not via electromagnetic radiation to any substantial extent.

[0267] In a further embodiment of the flowchart described with reference to the foregoing figures and Figure 11, a near-field wireless method is provided for transmitting power in dual modes at a variable resonant power signal oscillation frequency according to an adjustable transmission mode ratio

[1000] , the method comprising providing

[1010] a transmitter subsystem 12 including a power signal tuner module 26F and a transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 configured to resonate at the resonant power signal oscillation frequency; and providing

[1020] a receiver antenna subsystem 52, 152, 252, 352, 154, 254, 336 configured to resonate at the resonant power signal oscillation frequency. Receiver subsystem 14 of 54 and 356; provides a power signal self-tuner module 26F to transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 at the power signal oscillation resonant frequency

[1030] ; adjusts the transmission mode ratio

[1040] by adjusting the power signal from self-tuner module 26F to transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336; and receives the transmitted power at the transmission mode ratio

[1050] via receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356 at the power signal oscillation resonant frequency in receiver subsystem 14. Adjusting the transmission mode ratio

[1040] may include adjusting one of the phase differences between the current and voltage of the power signals provided to the transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336.

[0268] A transmitter subsystem 12

[1010] may further include a controller 22 and at least one sensor 24, and may adjust the phase difference between current and voltage by means of a command from the controller 22 via a tuner module 26F based on sensor information received by the controller 22 from at least one sensor 24. The command from the controller 22 may be automatically sent to the tuner module 26F after the controller 22 receives the sensor information; and the tuner module 26F may automatically execute the command from the controller 22 to change the phase difference.

[0269] The method

[1000] may further include allowing

[1060] the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an Industrial, Scientific, and Medical (ISM) band. Providing

[1010] a transmitter subsystem may include a transmitter subsystem that provides demodulation to a degree that allows the resonant power signal oscillation frequency to vary within the opposite limit of the predetermined frequency band.

[0270] In a further embodiment described with reference to Figures 12, 13A, and 13B and Figures 1 through 10, a multi-transmitter dual-mode near-field resonant wireless power transmission system 10' is configured to simultaneously perform capacitive and inductive power transmission at a variable resonant power signal oscillation frequency according to an adjustable transmission mode ratio. System 10' includes a multi-transmitter subsystem 12' comprising a plurality of transmitter resonators 30A' to 30I' each driven by a corresponding dedicated transmitter module 20A' to 20I', wherein each transmitter resonator and corresponding transmission module (e.g., 30E' and 20E', respectively) conforms to the description given above and with reference to Figures 1 through 10. Figure 12 is a schematic representation of one embodiment of system 10', wherein transmitter resonators 30A' to 30I' are presented as nine resonators in a row but are not depicted in their formal spatial positions. One embodiment of the spatial layout of the multi-transmitter subsystem 12′ is shown in Figures 13A and 13B and described below. In system 10′, the resonant receiver subsystem 14 may be the same as or substantially similar to the resonant receiver systems described above and mentioned in Figures 1 to 10. In the embodiment shown in Figure 12, the resonant receiver subsystem 14 may (e.g., but not limited to) be implemented in a mobile phone or a digital “tablet computer”. For simplicity, the resonant receiver subsystem 14 is depicted in dashed outline in Figure 13A. In one embodiment, each operating transmitter resonator 30A′ to 30I′ and each corresponding transmitter module 20A′ to 20I′ may operate in the same or substantially similar manner to the transmitter resonator 30 and transmitter module 20 described above and depicted in Figures 1 to 10. One embodiment of the spatial layout of the multi-transmitter subsystem 12′ is depicted in Figures 13A and 13B. Figure 13B is a view of the multitransmitter subsystem 12′ in a reverse orientation relative to its orientation in Figure 13A.

[0271] In an exemplary embodiment of the system 10' shown in Figures 12, 13A, and 13B, the multi-transmitter subsystem 12' includes nine pairs of transmitter resonators 30A' to 30I' and corresponding transmitter modules 20A' to 20I' arranged in a square array. Transmitter modules 20A' to 20I' are obscured by a grounding plate 35' in Figure 13A but are visible in Figure 13B. In a more general embodiment, other numbers of resonator pairs and transmitter modules may be used, and the resonator array need not be square or rectangular. By way of example and not limitation, the resonator array may have a hexagonal configuration. In some embodiments, the array is preferably tightly packed within a constraint having a grounding grid that separates and delimits the transmitter resonators 30A' to 30I'. The grounding grid 33' laterally restricts the array of transmitter resonators 30A' to 30I'. A grounding shield 33' is positioned at a consistent distance 37' from the periphery of each of the transmitter resonators 30A' to 30I' to ensure consistent electric field behavior and associated capacitance between the transmitter resonators 30A' to 30I' and the grounding shield 33'. The term "shielding distance" is used herein to describe this distance between the resonators 30A' to 30I' and the grounding shield 33'.

[0272] In one embodiment, the grounding grid 33' ensures that the electric fields of the transmitter resonators 30A' to 30I' are completely spatially decoupled and thus spatially independent. The transmitter resonators 30A' to 30I' may have magnetic fields selected to decouple each other by means of spatial orientation. In other embodiments, the grounding grid 33' may be formed of or coated with a highly conductive ferrite material to decouple the magnetic fields generated by the transmitter resonators 30A' to 30I'.

[0273] As shown in Figures 13A and 13B, the transmitter resonators 30A′ to 30I′ and their corresponding transmitter modules 20A′ to 20I′ can be mounted substantially in a straight line to each other on opposite surfaces of the grounding base plate 35′, wherein each transmitter resonator (e.g., 30E′) is close to its corresponding transmitter module (20E′). In other embodiments, there may be no fixed spatial relationship between the transmitter resonators and their corresponding transmitter modules. The array of transmitter resonators 30A′ to 30I′ shares a common transmission surface defined by the common upper surface of the transmitter resonators 30A′ to 30I′ in Figure 13A. For aesthetic and protective reasons, the array of transmitter resonators 30A′ to 30I′ may be covered by a dielectric plate not shown in Figure 13A. The dielectric plate separates the receiver subsystem 14 from the transmitter resonators 30A′ to 30I′.

[0274] In Figures 12 and 13A, one embodiment of the resonant receiver subsystem 14 is schematically shown as a subset of overlapping transmitter resonators 30A′ to 30I′. According to Figures 12 and 13A, the overlapping transmitter resonators are shown as 30D′, 30E′, 30G′, and 30H′. In Figure 13A, the resonant receiver subsystem 14 is shown as a dashed rectangle above mutually adjacent transmitter resonators 30D′, 30E′, 30G′, and 30H′. The controller of any of the transmitter modules 20A′ to 20I′ can determine the presence or absence of the resonant receiver subsystem 14 that is close to or overlaps with its corresponding transmitter resonators 30A′ to 30I′, and based on such detection, the controller can turn on or off the power signals to its corresponding transmitter resonators 30A′ to 30I′.

[0275] If the power amplifiers of the transmitter modules 20A′ to 20I′ supply power signals to the transmitter resonators 30A′ to 30I′ so that the transmitter resonators 30A′ to 30I′ transmit power, and the controllers of the transmitter modules 20A′, 20B′, 20C′, 20F′ and 20I′ determine that there is no resonant receiver within the frequency range of the transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′, then the controllers may shut off the power signals to the transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′.

[0276] If the power amplifiers of transmitter modules 20A′ to 20I′ do not supply power signals to transmitter resonators 30A′ to 30I′, the controllers for transmitter resonators 30D′, 30E′, 30G′, and 30H′ can determine the presence of resonant receiver subsystem 14 that overlaps with and is close to resonators 30D′, 30E′, 30G′, and 30H′, and connect the transmittable power supplied to transmitter resonators 30D′, 30E′, 30G′, and 30H′ via transmitter modules 20D′, 20E′, 20G′, and 20H′. This configuration ensures that only transmitter resonators close to resonant receiver subsystem 14 draw power and transmit power to resonant receiver subsystem 14.

[0277] The input impedance of a specific transmitter resonator 30A′ to 30I′ can be used to detect the presence or absence of a resonant receiver subsystem 14 near the specific transmitter resonator. The input impedance of the transmitter resonator varies with the presence or absence of a resonant receiver subsystem 14 near the specific transmitter resonator. As explained above with reference to Figure 6, the effects of the specific resonant receiver subsystem 14 are different so as to allow not only the detection of the presence or absence of the receiver but also the detection of characteristics that allow the type of receiver to be identified by its effect on the input impedance of the transmitter resonator. Specifically, the size of the receiver resonator has a profound effect on the input impedance of a specific transmitter resonator 30A′ to 30I′.

[0278] In one embodiment of system 10′, the transmitter module 20E′ depicted in Figures 12 and 13B is associated with one of the four transmitter resonators 30D′, 30E′, 30G′, and 30H′ overlapped by the resonant receiver subsystem 14. Detailed structures of each of the transmitter modules 20A′ to 20I′ are provided in Figures 6 and 8. The program begins when the power amplifier 26B of the transmitter modules 20A′ to 20I′ does not provide power signals to the corresponding transmitter resonators 30A′ to 30I′.

[0279] Now focusing on the transmitter module 20E′, in this embodiment, its load detector 24A is configured to measure the input impedance of the transmitter resonator 30E′. The load detector 24A provides the input impedance measurement result to the controller 22. A preset input impedance measurement value, representing the input impedance of the transmitter resonator 30E′ in the absence of any resonant receiver subsystem near the transmitter resonator 30E′, is stored in a register in the controller 22. As shown in FIG12, the placement of the resonant receiver subsystem 14 near the transmitter resonator 30E′ results in a new and different input impedance measurement by the load detector 24A, the result of which is supplied to the controller 22 by the load detector 24A. The controller 22 compares the new input impedance measurement (referred herein to as "first input transmitter resonator impedance change" or "primary transmitter resonator input impedance change") with the preset impedance measurement value stored in the register. Based on this first input impedance change, the controller 22 makes a determination about whether a receiver resonator (e.g., the resonator of the resonant receiver subsystem 14) is close to the presence of the transmitter resonator 30E′. In order to make a determination about the absence or presence of a receiver resonator close to the transmitter resonator 30E′, the controller 22 can use a pre-programmed minimum input impedance change that must exceed a certain threshold before the controller 22 considers a receiver resonator to be present.

[0280] If the controller 22 determines that a receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) is near the transmitter resonator 30E', ​​the controller 22 instructs the power amplifier to enter an "on" state. Power is thus supplied to the transmitter resonator 30E' and subsequently transmitted to the resonant receiver subsystem 14. If the controller 22 determines that no receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) is near the transmitter resonator 30E', ​​the controller 22 instructs the power amplifier to enter an "off" state. Power is thus not supplied to the transmitter resonator 30E' and subsequently not transmitted to the resonant receiver subsystem 14. The same procedure is performed independently by each transmitter module 20A' to 20I' relative to its corresponding transmitter resonators 30A' to 30I'. Therefore, the power amplifiers of the transmitter modules 30D′, 30E′, 30G′ and 30H′ overlapped by the resonant receiver subsystem 14 are turned on, and the power amplifiers of the transmitter modules 30A′, 30B′, 30C′, 30F′ and 30I′ not overlapped by the resonant receiver subsystem 14 are turned off.

[0281] It should be noted that receiver resonators of different sizes present distinct impedances at point 24A to the load detector 24A of transmitter module 20. The measured resonance difference when a given receiver resonator fully overlaps a particular transmitter resonator is not as distinctly different from the impedance measured when the receiver resonator partially overlaps the transmitter resonator, as the impedance varies with the size of the receiver resonator. This allows the controller 22 of any transmitter module 20A′ to 20I′ to distinguish between small and large receiver resonators approaching the corresponding transmitter resonators 30A′ to 30I′.

[0282] According to one embodiment, the setting of the frequency and phase of the power signals in the transmitter resonators (e.g., 30D′, 30E′, 30G′, and 30H′) superimposed by a resonant receiver subsystem (e.g., resonant receiver subsystem 14) is described herein. For maximum effective transmission of power from the combination of power-receiving transmitter resonators 30D′, 30E′, 30G′, and 30H′, the power signals in the resonators 30D′, 30E′, 30G′, and 30H′ need to have the same frequency and, moreover, be in phase. Given that the frequencies of the electrical signals in the transmitter resonators 30D′, 30E′, 30G′ and 30H′ may differ within an permissible frequency band, as previously described above and with reference to Figures 1 to 10, the requirement in this embodiment of Figures 12, 13A and 13B is to adjust the frequencies of the electrical signals in the transmitter resonators 30D′, 30E′, 30G′ and 30H′ to be the same and then lock them in phase so that the electrical signals from the transmitter resonators 30D′, 30E′, 30G′ and 30H′ will be completely synchronized and in phase.

[0283] In one embodiment, to ensure that the controllers 22 of the overlapping transmitter resonators 30D′, 30E′, 30G′, and 30H′ all set their corresponding oscillators 26A to the same frequency, the controllers 22 of the transmitter modules 20A′ to 20I′ all have an identical table of frequencies selected within any given permissible frequency band (e.g., an ISM band). Within this particular ISM band, several discrete frequencies are selected to be included in the frequency table. Therefore, the number of frequencies used to create the table within the ISM band is finite and limited, and the intervals between the frequencies in the table are sufficiently wide so that the various controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ can determine a power signal frequency from the first impedance difference described above. Despite the slight variations in impedance, all controllers of transmitter modules 20D′, 20E′, 20G′ and 20H′ select the same discrete frequency for the power signals of their respective oscillators 26A and power amplifiers 26B within the permissible frequency range of the frequency band.

[0284] In one embodiment, to ensure that the resonators 30D′, 30E′, 30G′, and 30H′ all have not only the same power signal frequency but also the same phase, the following procedure is adopted and programmed into the software of each controller 22 of the transmitter modules 20A′ to 20I′. Statistically, the first of the independent controllers 22 among the independent controllers of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will first turn on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second of the other independent controllers 22 among the independent controllers of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will measure the input impedance of its corresponding transmitter resonator and detect a small secondary change in impedance attributable to the function of the first transmitter resonator by its corresponding load detector 24A. In practice, the second controller 22 observes a reflection of the impedance of the first transmitter resonator through the interaction between the first transmitter resonator and the resonant receiver subsystem 14. The second controller 22 is programmed to deduce that, based on the secondary impedance change, another controller has first turned on its oscillator 26A and power amplifier 26B. After making this deduction, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and changes the phase of its power signal, while simultaneously using its transmitter power sensor 24B to measure the power transmitted by its corresponding transmitter resonator. The second controller 22 then changes the phase of its oscillator and searches for the phase where maximum power transmission occurs, setting the oscillator phase to that value. The oscillator phase determined in this way ensures that the phase of the power signal transmitted by the second transmitter resonator is equal to the phase of the power signal transmitted from the first transmitter resonator to the resonant receiver subsystem 14. In one embodiment, the oscillator phase setting is based on substantially maximizing power transmission rather than absolutely equalizing the power signal phase.

[0285] In another embodiment, the proximity detection of the resonant receiver subsystem 14 is again based on the overlap of the transmitter resonators 30D′, 30E′, 30G′, and 30H′ via the resonant receiver subsystem 14. The proximity detection of the resonant receiver subsystem 14 is based on the test signal power drawn through the transmitter resonators 30D′, 30E′, 30G′, and 30H′. In this embodiment, the low-amplitude power signal is initially maintained by oscillators and power amplifiers corresponding to all transmitter resonators 30A′ to 30I′. The controller 22 of all transmitter modules 20A′ to 20I′ then uses its corresponding transmitter power sensor 24B to sense the power drawn through its corresponding transmitter resonator 30. Using its corresponding transmitter power sensor 24B, the controller 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ senses the power drawn through their corresponding transmitter resonators 30D′, 30E′, 30G′, and 30H′. Based on the detection of the power drawn from the test signal, the controllers 22 of transmitter modules 20D′, 20E′, 20G′, and 20H′ turn on the full power of their corresponding power amplifiers 26B. The term "first test signal draw" is used herein to describe this power drawn from the test signal via transmitter resonators 30D′, 30E′, 30G′, and 30H′. The test power signals of the power amplifiers 26B of transmitter modules 30A′, 30B′, 30C′, 30F′, and 30I′ that are not superimposed on the resonant receiver subsystem 14 can be turned off after a suitable test cycle.

[0286] Equivalent to the impedance-based embodiment described above, the controller 22 of the transmitter modules 20D′, 20E′, 20G′ and 20H′ may require a critical power draw to assume that the resonant receiver subsystem 14 is close to the presence of its corresponding transmitter resonators 30D′, 30E′, 30G′ and 30H′.

[0287] In one embodiment, to ensure that the controllers 22 of the overlapping transmitter resonators 30D′, 30E′, 30G′, and 30H′ all set their corresponding oscillators 26A to the same frequency, the controllers 22 of the transmitter modules 20A′ to 20I′ all have an identical table of frequencies selected within any given permissible frequency band (e.g., an ISM band). Within this particular ISM band, several discrete frequencies are selected to be included in the frequency table. Therefore, the number of frequencies used to create the table within the ISM band is finite and limited, and the intervals between the frequencies in the table are sufficiently wide so that the various controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ can determine a power signal frequency from the first test signal power described above. Despite minor variations in these power draw values, all controllers 22 of transmitter modules 20D′, 20E′, 20G′ and 20H′ select the same discrete frequency for the power signals of their respective oscillators 26A and power amplifiers 26B within the permissible frequency range of the frequency band.

[0288] In one embodiment, to ensure that the resonators 30D′, 30E′, 30G′, and 30H′ all have not only the same power signal frequency but also the same phase, the following procedure is adopted and programmed into the software of each controller 22 of the transmitter modules 20A′ to 20I′. Statistically, the first of the independent controllers 22 of the independent controllers of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will first turn on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second of the other independent controllers 22 of the independent controllers of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will measure the power draw of its corresponding transmitter resonator and detect a small secondary change in the power draw attributable to the function of the first transmitter resonator by its corresponding transmitter power sensor 24B. In practice, the second controller 22 observes a reflection of the impedance of the first transmitter resonator through the interaction between the first transmitter resonator and the resonant receiver subsystem 14. The second controller 22 is programmed to deduce that, based on secondary changes in power extraction, another controller has first activated its oscillator 26A and power amplifier 26B. After making this deduction, the second controller 22 then activates its oscillator 26A and power amplifier 26B and modifies the phase of its power signal, while simultaneously measuring the power transmitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then searches for the phase in which maximum power transfer occurs and sets the oscillator to that phase. This oscillator phase setting ensures that the phase of the power signal transmitted from the second transmitter resonator to the resonant receiver subsystem 14 is equal to the phase of the power signal transmitted from the first transmitter resonator to the resonant receiver subsystem 14. In this embodiment, the oscillator phase setting is based on substantially maximizing power transfer rather than absolutely equalizing the power signal phase.

[0289] In one embodiment, when two different resonant receiver subsystems are close to the multitransmitter subsystem 12' and overlap different or combined transmitter resonators 30A' to 30I', there is no a priori reason why the two different transmitter resonators or groups of two different transmitter resonators overlapping the two resonant receiver systems should operate at the same frequency or phase, or there is no requirement to do so. The grounding shield 33' ensures this multiplexing independence by decoupling all individual transmitter resonators 30A' to 30I' from each other. However, the overlapping transmitter resonators of a particular resonant receiver subsystem require their corresponding power signal amplifiers to be actively synchronized by their controllers, as described above. This can result in two different transmitter resonators, or two different groups of resonators, operating at two specific different locked frequencies in a frequency band, wherein all signals in a particular group are in phase with each other.

[0290] As described above, it has been described how two transmitter resonators transmitting power to the same receiver resonator can be programmed to ensure that the two transmitter resonators carry in-phase power signals to ensure maximum power transmission. A different scenario arises when two adjacent transmitter resonators (i.e., 30A′ and 30B′ in Figure 14) transmit to two substantially similar corresponding receiver subsystems 14A and 14B. Both transmitter resonators 30A′ and 30B′ have edge fields whose field lines extend from, for example, transmitter resonator 30A′ to receiver subsystem 14B′ and from transmitter resonator 30B′ to receiver subsystem 14A. Typically, there is no specific physical structure in system 10′ to prevent, for example, the field of transmitter resonator 30A′ from interacting with the receiver resonator of receiver subsystem 14B.

[0291] In one embodiment, when both transmitter resonators 30A′ and 30B′ serve overlapping receiver resonators of the same large transmitter resonators 30A′ and 30B′ (as shown in FIG. 13A), edge fields are inherently not a problem because the two transmitter resonators 30A′ and 30B′ will operate with the same frequency electrical signal in the same phase. In the scenario depicted in FIG. 14, the requirement is to ensure that any edge field of a given transmitter resonator (e.g., 30A′) interacting with a receiver subsystem (e.g., 14B intended for receiving power from an adjacent transmitter resonator 30B′) does not allow power parasitism from transmitter resonator 30A′. One way to achieve this goal is to drive the two adjacent transmitter resonators 30A′ and 30B′ out of phase by 180⁰, such that the overlapping edge fields from transmitter resonators 30A′ and 30B′ will largely cancel each other out.

[0292] Since the power signals of transmitter resonators 30A′ and 30B′ are not out of phase by 180°, either transmitter resonator 30A′ or 30B′ will experience the other transmitter resonator 30A′ or 30B′ as a parasitic signal. Therefore, the controller 22 of each transmitter resonator 30A′ and 30B′ can measure the phase of the signal of the corresponding oscillator of each when the power transmitted through the corresponding transmitter resonators 30A′ and 30B′ is measured using the corresponding transmitter power sensor 24B. The controller 22 can then search for the phase of the adjusted oscillator that provides the maximum transmitted power through the corresponding transmitter resonators 30A′ and 30B′, and then set the phase of the oscillator to that corresponding phase.

[0293] The frequency and phase configuration of each resonant receiver system as described above (whether of similar or different sizes) ensures that the two resonant receiver systems receive maximum transmitted power. In a typical embodiment, there may be a large number of transmitter resonators and several different resonant receiver subsystems that can receive power. Each resonant receiver subsystem receives power from its own corresponding individual transmitter resonator group by means of a frequency and phase selected by a controller corresponding to the transmitter resonator in the group. Adjacent transmitter resonators that transmit power to different receiver subsystems can operate out of phase by 180⁰ due to the maximization of power transmission of each of the adjacent transmitter resonators. The procedure for maximizing power transmission adjusts the oscillator phase. Since the impedance of various transmitter modules is complex due to slight variations in resistance, inductance, and capacitance, the phase angles of different oscillators at the point of maximum power transmission may not be exactly equal (or differ by exactly 180⁰) when the power signals in the transmitter resonators are actually equal (or differ by exactly 180⁰).

[0294] As for system 10' including a circuit having an air gap between the primary and secondary sides, any power transfer measured or maximized in a transmitter resonator (e.g., based on the measurement of transmitter power sensor 24B at point 24E in FIG. 6) can also be measured or maximized in the secondary circuit (e.g., based on the measurement of receiver power sensor 44A at point 44C in FIG. 7). The measurement can be provided by transmitter power sensor 24B to controller 42 of receiver module 40, which can then transmit the measurement to controller 22 of transmitter module 20 by one of the means already described above.

[0295] The concept of a multi-transmitter near-field resonant wireless power transmission system has been explained above with reference to system 10', which is configured to simultaneously perform capacitive and inductive power transmission at a variable resonant power signal oscillation frequency according to an adjustable transmission mode ratio. In a more general embodiment, a multi-transmitter near-field resonant wireless power transmission system does not need to be explicitly a dual-mode system and can be a purely capacitive or purely inductive power transmission system.

[0296] In a further embodiment depicted in the flowchart of Figure 15, a wireless near-field method

[1100] for transmitting power from a multi-transmitter subsystem 12' to a single-resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency includes: providing

[1110] a multi-transmitter subsystem 12' comprising a plurality of independent transmitter resonators 30A' to 30I', each transmitter resonator being driven by a corresponding transmitter module 20A' to 20I', each transmitter module 20A' to 20I' being independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and All transmitter resonators 30A′ to 30I′ have a common transmission surface; a resonant receiver subsystem 14 comprising one or more of the overlapping transmitter resonators (30D′, 30E′, 30G′ and 30H in FIG. 13A) is arranged near the common transmission surface

[1120] ; a single receiver resonator 50 is installed; the input impedance of each of the transmitter resonators 30A′ to 30I′ is measured

[1130] ; and a power signal is set

[1140] to one of the plurality of independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator input impedance.

[0297] Method

[1100] may further include

[1150] selecting one of the power signal oscillation frequencies of the corresponding transmitter resonator (30D′, 30E′, 30G′ and 30H′ in FIG13A) from a plurality of preset power signal oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (resonators 30D′, 30E′, 30G′ and 30H′ in FIG13A).

[0298] The method

[1100] may further include setting

[1160] the power signal of each active transmitter resonator (30D′, 30E′, 30G′ and 30H′ in FIG13A) to the corresponding selected frequency.

[0299] The method

[1100] may further include adjusting

[1170] one phase of the power signal applied to each of the corresponding transmitter resonators (resonators 30D′, 30E′, 30G′ and 30H in FIG. 13A) to substantially the largest phase of the power transmission through the transmitter resonators (30D′, 30E′, 30G′ and 30H′ in FIG. 13A).

[0300] In a further embodiment depicted in the flowchart of Figure 16, a wireless near-field method

[1200] for transmitting power from a multi-transmitter subsystem 12' to a single-resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency includes: providing

[1210] a multi-transmitter subsystem 12' comprising a plurality of mutually independent transmitter resonators 30A' to 30I', each of the transmitter resonators being driven by a corresponding transmitter module 20A' to 20I', each transmitter module 20A' to 20I' being independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitters... Resonators 30A′ to 30I′ have a common transmission surface; a resonant receiver subsystem 14 comprising one or more of overlapping transmitter resonators (30D′, 30E′, 30G′ and 30H′ in FIG. 13A) is arranged near the common transmission surface

[1220] ; a single receiver resonator 50 is positioned to measure

[1230] the power drawn from a test signal by each of the transmitter resonators 30A′ to 30I′; and a power signal set

[1140] to one of the power signals drawn from each of the plurality of independent transmitter resonators 30A′ to 30I′ based on the power drawn from the corresponding measured resonator test signal is set to one of an off state and an active state.

[0301] The method

[1200] may further include selecting

[1250] one of the power signal oscillation frequencies corresponding to the transmitter resonator (30D′, 30E′, 30G′ and 30H in FIG13A) from a plurality of preset power signal oscillation frequencies based on the measured test power drawn from each of the active transmitter resonators (resonators 30D′, 30E′, 30G′ and 30H in FIG13A).

[0302] The method

[1200] may further include setting the power signal of each active transmitter resonator (30D′, 30E′, 30G′ and 30H in FIG13A)

[1260] to the corresponding selected frequency.

[0303] The method

[1200] may further include adjusting

[1270] one phase of the power signal applied to each of the corresponding transmitter resonators (resonators 30D′, 30E′, 30G′ and 30H in FIG13A) to one phase that is substantially the largest of the power transmission through the transmitter resonators (30D′, 30E′, 30G′ and 30H in FIG13A).

[0304] In a further embodiment depicted in the flowchart of Figure 17, a wireless near-field method for transmitting power from a multi-transmitter subsystem 12' to two or more receiver subsystems 14A, 14B (in Figure 14) at a variable resonant power signal oscillation frequency

[1300] includes: providing

[1310] a multi-transmitter subsystem 12' comprising a plurality of mutually independent transmitter resonators 30A' to 30I' (in Figure 14), each of the transmitter resonators being connected by a corresponding transmitter module 20A' to 20I'. (See Figure 13B) Driven, each transmitter module 20A′ to 20I′ can be independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ have a common transmission surface; two or more resonant receiver subsystems 14A, 14B, each including one or more single receiver resonators of overlapping transmitter resonators (transmitter resonators 30A′, 30B′ in Figure 14), are arranged near the common transmission surface; the input impedance of each of the transmitter resonators 30A′, 30B′ is measured; and based on the corresponding measured resonator input impedance, one of the power signals of each of the plurality of independent transmitter resonators 30A′ to 30I′ is set

[1340] to one of an off state and an active state.

[0305] The method

[1300] may further include

[1350] selecting one of the power signal oscillation frequencies of the corresponding transmitter resonator 30A′ and 30B′ from a plurality of preset power signal oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (resonators 30A′ and 30B′ in FIG14).

[0306] The method

[1300] may further include setting

[1360] the power signal of each active transmitter resonator 30A′, 30B′ to the corresponding selected frequency.

[0307] The method

[1300] may further include adjusting

[1370] one phase of the power signal applied to each of the corresponding transmitter resonators 30A′, 30B′ to one phase that is substantially the largest of the power transmission through the transmitter resonators 30A′, 30B′ (in FIG. 14).

[0308] In a further embodiment depicted in the flowchart of FIG18, a wireless near-field method for transmitting power from a multi-transmitter subsystem 12' to two or more receiver subsystems 14A, 14B (in FIG14) at a variable resonant power signal oscillation frequency

[1400] includes: providing

[1410] a multi-transmitter subsystem 12' comprising a plurality of mutually independent transmitter resonators 30A' to 30I' (in FIG14), each of the transmitter resonators being a corresponding transmitter module 20A' to 20I'. (See Figure 13B) Driven, each transmitter module 20A′ to 20I′ can be independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ have a common transmission surface; two or more resonant receiver subsystems 14A, 14B, each including one or more single receiver resonators of overlapping transmitter resonators (transmitter resonators 30A′, 30B′ in Figure 13), are arranged near the common transmission surface;

[1430] the power drawn from a test signal by each of the transmitter resonators 30A′ to 30I′ is measured; and based on the power drawn from the test signal by the corresponding measured resonator, one of the power signals of each of the plurality of independent transmitter resonators 30A′ to 30I′ is set

[1440] to one of an off state and an active state.

[0309] The method

[1400] may further include

[1450] selecting one of the power signal oscillation frequencies of the corresponding transmitter resonator 30A′ and 30B′ from a plurality of preset power signal oscillation frequencies based on the measured input impedance of each of the active transmitter resonators (resonators 30A′ and 30B′ in FIG14).

[0310] The method

[1400] may further include setting

[1460] the power signal of each active transmitter resonator 30A′, 30B′ to the corresponding selected frequency.

[0311] The method

[1400] may further include adjusting

[1470] one phase of the power signal applied to each of the corresponding transmitter resonators 30A′, 30B′ to one phase that is substantially the largest of the power transmission through the transmitter resonators 30A′, 30B′ (in FIG. 14).

[0312] Referring to Figures 20A and 20B, 21A and 21B, and 22A and 22B, and based on a further embodiment of the system description in Figures 1 to 10 and 12 to 14, a near-field resonant wireless power transmission system 10′′ for wirelessly transmitting power from a photovoltaic solar cell 420 to a power load 70′′ is shown in the schematic diagram of Figure 19A. An accented numbering system is used for the markings in Figure 19A, making the parallel lines in Figures 13A and 13B clear, and thereby also clear with the parallel lines in Figures 6 and 7. By means of this numbering scheme, DC power is supplied from the solar cell 420 to the transmitter module 20′′ via a power conditioning unit (PCU) 430. In addition to converting DC voltage and DC current into levels that can be further transmitted via power amplifier 26B′′, PCU 430 also provides appropriately regulated levels of voltage and current to drive the rest of the system components (including small-signal electronics) in transmitter module 20′′. PCU 430 represents an adaptive variable load of solar cell 420 to accommodate different power supplied by solar cell 420 and different output impedances presented to PCU 430 by solar cell 420. This allows PCU 430 to absorb power from solar cell 420 at a maximum possible rate throughout all time and temperature, despite variations in that power from solar cell 420.

[0313] Oscillator 26A′′ can be used in frequency-modulated power amplifier 26B′′ suitable for wireless power transmission, as described above. Power amplifier 26B′′ may have the same design as amplifier 26B shown in FIG8, wherein DC power is supplied from PCU 430 rather than as DC voltage 127E. In an alternative embodiment, as is well known in the field of radio systems, power amplifier 26B′′ may suitably include circuitry for maintaining one of its own oscillations, thereby eliminating oscillator 26A′′.

[0314] Power can be transmitted to the transmission resonator 30'' via the transmission tuning network 28'', which in FIG. 19A is an amalgamation of one of the signal conditioning and tuning components 26C, 26D, 26E, and 26F of FIG. 6. The transmission resonator 30'' may have a surface area that comprises at least a major portion of the active solar radiation receiving surface of the solar cell 420. All such components of the transmission module 20'' are under the control of the controller 22'', just as the corresponding components of the transmission module 20 in FIG. 6 are under the control of the controller 22. For clarity, not all components of the transmission module 20'' are shown in FIG. 19A. The sensors and detectors 24A, 24B, 24C, and 24D of FIG. 6 may also exist in the transmission module 20'' in an equivalent form and be connected to the controller 22'', fulfilling the same role as in FIG. 6.

[0315] Power can be wirelessly transmitted from transmitter module 20′′ to receiver module 40′′ via transmitter resonator 30′′ and receiver resonator 50′′. Power can then be transmitted from receiver module 40′′ to DC load 70′′. The transmission of power between transmitter resonator 30′′ and receiver resonator 50′′ can be via near-field wireless transmission, as described above with reference to Figures 6 to 10. The near-field wireless power transmission according to Figure 20 is not limited to dual-mode and can be purely capacitive or purely inductive.

[0316] Receiver module 40′′ may have the same components as receiver 40 in Figure 7. For clarity, a simplified set of these components is shown in Figure 19A. Sensors 44A and detectors 44B in Figure 7 are not shown in equivalent form in Figure 19A, but may be present. Receiver tuning network 48′′ in Figure 19A may be a combination of compensation network 46A, matching network 46B, rectifier 46D, and filter 46C. Power can be delivered from receiver tuning network 48′′ to load manager 46E′′, both of which are under the control of receiver controller 42′′.

[0317] Referring to FIG19A and based on the system description of FIG1 to FIG10, a near-field resonant wireless power transmission system 10′′ for wirelessly transmitting power from a power source (in this exemplary embodiment, a photovoltaic solar cell 420) to a power load 70′′ is presented. A dual-tone numbering system is used for the markings on FIG19A to make the parallel lines of FIG6 and FIG7 clear. By means of this numbering scheme, DC power is supplied from the solar cell 420 to the transmitter module 20′′ via a power conditioning unit (PCU) 430. In addition to converting DC voltage and DC current to levels suitable for conversion into radio frequency signals for further transmission by power amplifier 26B′′, PCU 430 also provides voltage and current at appropriately regulated levels to drive, for example, the rest of the system components (including small-signal electronic components) in the transmitter module 20′′. PCU 430 represents an adaptive variable load of solar cell 420 to accommodate different power supplied by solar cell 420 and different output impedances presented to PCU 430 by solar cell 400. This allows PCU 430 to absorb power from solar cell 420 at a maximum possible rate throughout all time and temperature, despite variations in that power from solar cell 420.

[0318] Oscillator 26A′′ can be used in frequency-modulated power amplifier 26B′′ suitable for wireless power transmission, as described above. Power amplifier 26B′′ may have the same design as amplifier 26B shown in FIG8, wherein DC power is supplied from PCU 430 rather than as DC voltage 127E. In an alternative embodiment, as is well known in the field of radio systems, power amplifier 26B′′ may suitably include circuitry for maintaining one of its own oscillations, thereby eliminating oscillator 26A′′.

[0319] Power can be transmitted to the transmission resonator 30'' via the transmission tuning network 28'', which in FIG. 19A is an amalgamation of one of the signal conditioning and tuning components 26C, 26D, 26E, and 26F of FIG. 6. The transmission resonator 30'' may have a surface area that comprises at least a major portion of the active solar radiation receiving surface of the solar cell 420. All such components of the transmission module 20'' are under the control of the controller 22'', just as the corresponding components of the transmission module 20 in FIG. 6 are under the control of the controller 22. For clarity, not all components of the transmission module 20'' are shown in FIG. 19A. The sensors and detectors 24A, 24B, 24C, and 24D of FIG. 6 may also exist in the transmission module 20'' in an equivalent form and be connected to the controller 22'', fulfilling the same roles as described with reference to FIG. 6.

[0320] Power can be wirelessly transmitted from transmitter module 20′′ to receiver module 40′′ via transmitter resonator 30′′ and receiver resonator 50′′. Power can then be transmitted from receiver module 40′′ to DC load 70′′. The transmission of power between transmitter resonator 30′′ and receiver resonator 50′′ can be via near-field wireless transmission, as described above with reference to Figures 6 to 10. The near-field wireless power transmission according to Figure 19A is not limited to dual-mode and can be purely capacitive or purely inductive.

[0321] Receiver module 40′′ may have the same components as receiver 40 in Figure 7. For clarity, a simplified set of these components is shown in Figure 19A. Sensors 44A and detectors 44B in Figure 7 are not shown in equivalent form in Figure 19A, but may be present. Receiver tuning network 48′′ in Figure 19A may be a combination of compensation network 46A, matching network 46B, rectifier 46D, and filter 46C. Power can be transferred from receiver tuning network 48′′ to load manager 46E′′, both of which are under the control of receiver controller 42′′.

[0322] Regarding the rectifier 46D, which is shown in more detail in Figure 7, the input impedance of this device depends directly on the load experienced by the output of the device.

[0323] In operation, the near-field resonant wireless power transmission system 10′′ can function in the same manner as the near-field resonant wireless power transmission system 10 of Figures 1 and 6 to 10, wherein the difference is that the applied voltage VDD on each power amplifier 26B′′ is replaced by a power signal from the power conditioning unit (PCU) 430, which in turn receives its power from the associated power source (in this embodiment, the solar cell 420).

[0324] In another embodiment, the power conditioning unit 430 may be omitted from the system shown in FIG19A, and the power delivery system 10′′ may be configured or operated to also function as a power conditioning system. This can be achieved by configuring the controller 22′′ in software to adjust one of the input DC equivalent resistances of the power amplifier 26B′′ based on a power level measured by the power sensor 24B of FIG6. The term “input DC equivalent resistance” is used here to describe the ratio of DC voltage to DC current at the DC terminal of the power amplifier 26B. Although the controller 22′′ will be adjusted based on a power measurement, it is expected that the maximum power point transmitted will be obtained when the input impedance of the power amplifier 26B′′ matches the output impedance of the solar cell 420. In this embodiment, the system 10′′ functions as an industrially known “maximum power point tracker” and ensures that power is always transmitted at a rate more suitable for the power-consuming load than would be obtained under unregulated power supply conditions. In another embodiment, the controller 22′′ can be configured to measure the output impedance of the power supply (in this embodiment, the solar cell 420) and then adjust the input impedance of the power amplifier 26B′′ based on the measured output impedance of the solar cell 420.

[0325] In addition to adjusting the input impedance of the power amplifier 26B′′, the controller 22′′ can also adjust one or more settings of the transmitter tuning network 28′′ and the frequency of the oscillator 26A′′. Furthermore, the transmitter controller 22′′ can perform the adjustments described above based on measurements taken by the load detector 24A shown in Figure 6, which provides further details of the circuitry of transmitter modules 20 and 20′′. The load detector 24A senses the effect of the load 70′′ at point 24E in Figure 6.

[0326] The receiver controller 42′′ can also adjust one or more of the settings of the receiver tuning network 48′′ and the load management system 46E′′ in order to improve the efficiency of power transmission based on measurements performed by the receiver power sensor 44A and the load detector 44B (both shown in Figure 7).

[0327] When considering the power regulation function of system 10′′, it should be understood that there is no a priori reason why the power transmission function of the system should be limited to near-field wireless transmission across an air gap as shown in Figure 19A. Therefore, in another embodiment, a power regulation unit 410 is shown in Figure 19B based on the components of system 10′′ of Figure 19A. The transmitter tuning network 28′′ communicates directly with the receiver tuning network 48′′ via a suitable non-air gap connection 60′′. This communication is via a radio frequency power signal and constitutes the power transmitted in and by the system. Suitable reactive electronic components can be well configured to decouple any DC voltage and current levels in the transmitter module 20′′ from such levels in the receiver module 40′′. The transmitter resonator 30′′ and the receiver resonator 50′′ are not present in this embodiment and are excluded by the direct communication connection between the transmitter tuning network 28′′ and the receiver tuning network 48′′.

[0328] The power transmission systems of Figures 19A and 19B can be better understood as power conditioning systems by considering Figure 19B. Specifically, the power conditioning concept is simplified in that the transmitter resonator 30′′ and receiver resonator 50′′ are absent, although this applies equally to cases where such resonators are present (as in Figure 19A). The systems of Figures 19A and 19B have four independent control parameters that can be adjusted during operation to regulate the power transmitted to the receiver module 40′′ and thereby to the load 70′′. Typical commercial power conditioning units are often referred to as "boost converters" by boosting their output voltages above the source voltage. These devices have only two control parameters.

[0329] The first independent control parameter that can be adjusted during operation to regulate the power transmitted to the receiver module 40′′ and thereby to the load 70′′ is the oscillation frequency of the power amplifier 26B′′, which can be adjusted by the controller 22A′′ in the oscillator 26A′′.

[0330] The second independent control parameter that can be adjusted during operation to regulate the power transmitted to receiver module 40′′ and thereby to load 70′′ is the output load on rectifier 46D of receiver module 40′′. This output load then directly determines the input impedance of rectifier 46D and, consequently, receiver module 40′′. This, in turn, is the load experienced by transmitter module 20′′ and directly determines the input DC equivalent resistance of power amplifier 26B′′. The manipulation of the output load on rectifier 46D is accomplished by the load management system 46E′′ of receiver module 40′′ (see Figure 19A) under the control of receiver controller 42′′. This second independent control parameter is a property of the receiver module, but it inherently controls the load experienced by the power supply. The control point for manipulating this parameter is the load management system 46E′′ of receiver module 40′′.

[0331] The third and fourth independent control parameters that can be adjusted during operation to regulate the transmission to receiver module 40′′ and thereby to load 70′′ are properties of rectifier 46D in receiver module 40′′ (see Figure 7) and power amplifier 26B′′ (Figure 19A), and are essentially similar but completely independent of each other. Both rectifier 46D and power amplifier 26B′′ include multi-terminal amplifiers that rely on a current to modulate a voltage signal applied to a third terminal of each device through the multi-terminal device. The simplest multi-terminal amplifier that can be used in either rectifier 46D or power amplifier 26B′′ is a transistor. This allows for a phase difference between the voltage signal and the current signal generated by or within the device. This voltage-current phase difference can be adjusted by applying a voltage. Rectifier 46D can be an adjustable phase RF rectifier whose voltage-current phase difference can be adjusted by receiver controller 42′′. In the case of power amplifier 26B′′, the voltage-current phase difference can be adjusted via transmitter controller 22′′. Rectifier 46D may usefully include a differential self-synchronizing radio frequency rectifier. Rectifier 46D may particularly include a differential switching mode self-synchronizing radio frequency rectifier.

[0332] The examples in Figures 19A and 19B are based on the transmission of power from a solar cell or, in extension, a solar cell array, wherein the power delivered by solar cell 420 can vary significantly downward to zero depending on sunlight. Many other power sources exist that exhibit variable outputs in both power and the voltage produced. These include generator turbines, wind turbines, and various battery packs and storage batteries. Wind turbines can vary significantly in their power generation, and various battery packs can have a wide range of power depletion curves. Given the efficiency of the power transmission of the system, either of these systems 10′′ and 410 can be configured to receive power from (e.g., but not limited to) a commercial battery pack with a slow open-circuit voltage decay curve. The load management system 46E′′ can be configured to change the input DC equivalent resistance of the power amplifier 26B′′, as explained above, and the controllers 22′′ and 42′′ can be configured to present a desired voltage level to the load 70′′ until this voltage can no longer be maintained by the power transmission and the adjustability of the parameters of the system 10′′ and 410.

[0333] Figure 19A and its associated descriptive text address near-field wireless power transmission from a single solar cell 420 to a single load 70′′ (typically a battery pack). In practical implementations of larger solar cell power systems, battery arrays are typically used, allowing for power transmission schemes similar to those described with reference to Figures 12, 13A, and 13B, with multiple transmitter subsystems and typically a single receiver subsystem. This scenario is illustrated in Figures 20A and 20B, which are exploded front and rear views, respectively, of a solar panel 400 having a transparent solar cover 440. Each solar cell 420 has a near-field wireless power transmission subsystem, thereby including (by example) sixty near-field wireless power transmission subsystems 16, each including a transmitter resonator 30′′, a transmitter module 20′′, and a power conditioning unit 430 as described with reference to Figure 19A. To avoid clutter, the transmission subsystem 16 is not labeled in Figure 19A, but is indicated and labeled in Figures 20B, 21B and 22B, as further described below.

[0334] In one embodiment, the coupling of individual solar cells of a solar panel composed of a plurality of solar cells to a power transmission and management system allows for cell level power management. By providing power management at individual cell levels, power harvesting at each cell can be optimized, resulting in improved efficiency of the entire solar panel system. In this embodiment, the effects attributable to individual cell failure or poor connection of one of the cells are mitigated. Even in less desirable conditions (such as rain, darkness, or when debris covers part of the solar panel), power harvesting at individual cell levels still allows for maximum power gain.

[0335] To avoid clutter, only one near-field wireless power transmission subsystem 16 is labeled in Figure 20B. In Figures 20A and 20B, the transmitter resonator 30′′ of each transmission subsystem 16 can be positioned on the back side of its corresponding solar cell 420. The flat area of ​​the solar cell as seen from the front of the panel in Figure 20A represents the active solar radiation receiving and energy conversion semiconductor device itself and is correspondingly labeled 420, while the flat area of ​​the device as seen from the back side in Figure 20B represents the transmitter resonator and is correspondingly labeled 30′′. The transmitter resonator 30′′ may have a surface area that includes at least a major portion of the active solar radiation receiving surface of the solar cell 420. The transmitter module 20′′ and power conditioning unit 430 of each near-field wireless power transmission subsystem 16 are combined in Figure 20B and labeled 450. To avoid clutter, the merged component 450 is not labeled in Figure 19A, but is indicated as a unit and labeled in Figures 20B, 21B, and 22B, as further described below. A single receiver resonator 50′′ can be mounted in the frame 460 of the solar panel 400. A single receiver module 40′′ can be directly mounted on the back of the receiver resonator 50′′.

[0336] In operation, the near-field resonant wireless power transmission system 10′′ can function in the same manner as the near-field resonant wireless power transmission system 10′ of Figures 12, 13A and 13B, wherein the difference is that the applied voltage VDD on each of the power amplifiers 26B′′ is replaced by a power signal from the power conditioning unit (PCU) 430, which in turn receives its power from the associated solar cell 420.

[0337] In another embodiment of the system of Figures 20A and 20B, the frame 460 may be configured as a suitable receiver resonator for receiving power from all transmitter resonators 30′′, and the receiver module 40′′ may be positioned on the frame 460. In this embodiment, the plate within the frame is not a resonator and may be a simple flat sheet of non-conductive material.

[0338] In another embodiment, the solar panel 400' shown in the front and rear views of Figures 21A and 21B, respectively, enables each near-field wireless power transmission subsystem to transmit power to a near-field wireless power receiver subsystem. Although the frame 460 is shown as being filled by an opaque plate 470, the plate 470 may not be part of the near-field circuitry or magnetic circuitry. For clarity, we use the same component numbering on the transmitting side as in Figures 20A and 20B. On the receiving side, we use the numbering from Figure 19A. Furthermore, to avoid clutter, only one receiving-side device is labeled.

[0339] In operation, the solar panel configuration 400' of Figures 21A and 21B allows individual transmitter modules 20'' to be connected by hardwires (not shown) so that they are in phase, thereby allowing for minimal power loss during transmission. In other embodiments, the transmitter modules 20'' may be independent and operate as explained by Figures 14, 17 and 18.

[0340] In another further embodiment of the solar panel configuration 400′′ shown in the front and rear views of Figures 22A and 22B respectively, an array of, for example, twenty-five solar cells are shown, arranged in five columns, with five cells 420 in each column. Each solar cell 420 has a transmitter resonator 30′′ and a unit 450 including its corresponding transmitter module 20′′ and a power conditioning unit 430 at its rear. At the bottom and top of the array and between every two columns of solar cells, a receiver resonator 50′′ is disposed in a plane substantially perpendicular to the plane of the solar cells 420, and each receiver resonator 50′′ is in wired communication with its corresponding receiver module 40′′. As with the previous solar panel embodiments, an example of each component is labeled. As with the embodiments shown in Figures 20A and 20B and Figures 21A and 21B, in some embodiments, the solar panel configuration 400′′ may also have a frame 460. For clarity, frame 460 is not shown in Figures 22A and 22B.

[0341] In operation, the transmitter resonator 30'' of a specific column of solar cells 420 in system 400'' transmits power to the receiver resonators 50'' above and below it. However, in this embodiment, there is an additional mechanism where various nearest-neighbor receiver resonators 50'' are resonantly coupled and share the harvested power among them. Therefore, the harvested power collected by all the receiver resonators 50'' of the array can be tapped via any one or more of the various receiver modules 40''. Specifically, the power collected by all the receiver modules 40'' can (by example) be tapped only via the bottommost receiver module 40''. Any receiver module 40'' on any resonator 50'' can act as a receiver module to harvest power from a column of solar cells 420 and also as a transmitter module to transmit the harvested power via its associated resonator 50'' to another nearby resonator 50''. This action can be repeated along the array to transfer power to the bottom receiver module 40′′.

[0342] In another embodiment of the system of Figures 22A and 22B, similar to the frame 460 of Figures 20A and 20B, a frame surrounding the planar periphery of the solar cell arrays of Figures 22A and 22B may carry a receiver resonator of a receiver module 40′′ and receive power from various resonators 50′′. In this way, the total power generated by all the solar cells 420 in the array can be received by the resonator frame 460 and tapped for further electrical transmission via the receiver module 40′′.

[0343] Power collection at individual solar cell layers can be accomplished using a wired connection. However, using a wireless transmission system in solar panels allows for a reduction in wiring and thus a decrease in manufacturing costs.

[0344] In a further embodiment of the flowchart described with reference to FIG23, a method

[1500] for transmitting power from a photovoltaic cell 420 to an electrical load 70′′ is provided, the method comprising: converting

[1510] the power from the photovoltaic cell 420 into an oscillating power signal having an oscillation frequency in a transmission module 20′′; transmitting

[1520] the power to a transmitter that is in wired communication with the transmission module 20′′ and configured to resonate at the oscillation frequency. The method includes: receiving power

[1530] in a receiver resonator 50'', which is configured to resonate at an oscillation frequency and is positioned to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction; receiving power

[1540] in a receiver module 40'' in wired communication with the receiver resonator 50''; and presenting the received power in DC form

[1550] to a power load 70'' via wired communication. The method may further include converting a voltage and a current of the power from the photovoltaic cell 420 into a voltage and a current suitable for the transmission module 20'' before converting the power from the photovoltaic cell 420 into an oscillating power signal.

[0345] In a further embodiment of the method described with reference to the flowcharts in Figures 19A and 24, a method

[1600] for transmitting power from an array 400 of photovoltaic cells 420 to an electrical load 70′′ is provided, the method comprising: converting

[1610] power from each of the photovoltaic cells 420 in the array 400 into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmission modules 20′′; transmitting

[1620] power from each of the transmission modules 20′′ to a load 70′′ configured to resonate at the oscillation frequency. One of the second plurality of transmitter resonators 30′′ corresponds to a transmitter resonator 30′′; receives power in a receiver resonator 50′′

[1630] , the receiver resonator 50′′ being configured to resonate at an oscillation frequency and being positioned to receive power from the plurality of transmitter resonators 30′′ via at least one of capacitive coupling and magnetic induction; receives power in a receiver module 40′′ in wired communication with the receiver resonator 50′′

[1640] ; and presents the received power in DC form to a power load 70′′ via wired communication

[1650] . The method may further include converting a voltage and a current of the power from each photovoltaic cell 420 into a voltage and a current suitable for a corresponding transmission module 20′′ before converting the power from each photovoltaic cell 420 into an oscillating power signal. Receiving power in a receiver resonator 50′′

[1630] may include receiving power in a receiver resonator positioned around a plane periphery of the array of photovoltaic cells 400.

[0346] In a further embodiment of the method described with reference to the flowcharts in Figures 19A and 25, a method

[1700] is provided for transmitting power from an array 400' of photovoltaic cells 420 to an electrical load 70'', the method comprising: converting

[1710] power from each of the photovoltaic cells 420 in the array 400' into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmission modules 20''; transmitting

[1720] power from each of the transmission modules 20'' to a corresponding transmission resonator 30'' from a second plurality of transmission resonators 30'', where Each transmitter resonator 30′′ is configured to resonate at an oscillation frequency; power is received from each transmitter resonator 30′′ in a corresponding receiver resonator 50′′ configured to resonate at an oscillation frequency

[1730] , wherein each receiver resonator 50′′ is further configured and positioned to receive power from the transmitter resonator 30′′ via at least one of capacitive coupling and magnetic induction; power is received from each receiver resonator 50′′ in a corresponding receiver module 40′′ in wired communication with the receiver resonator 50′′

[1740] ; and the received power is presented as DC power to the power load 70′′ via wired communication

[1750] . The method may further include converting a voltage and a current of the power from each photovoltaic cell 420 into a voltage and a current suitable for the corresponding transmission module 20′′ before converting the power from each photovoltaic cell 420 into an oscillating power signal.

[0347] In a further embodiment described with reference to the flowcharts in Figures 19A and 26, a method

[1800] is provided for transmitting power from an array 400′′ of photovoltaic cells 420 to a power load 70′′ (in Figure 19A), the method comprising: converting

[1810] power from each of the photovoltaic cells 420 in the array 400′′ into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmission modules 20′′; transmitting

[1820] power from each of the transmission modules 20′′ to one of a second plurality of transmitter resonators 30′′, wherein each transmitter resonator 30′′ is configured to resonate at the oscillation frequency; and a third plurality of receiver resonators 50′ configured to resonate at the oscillation frequency.

[1830] Power is received from each transmitter resonator 30'' in any of the receiver resonators 50'', wherein each receiver resonator 50'' is further configured and arranged to receive power from the transmitter resonator 30'' via at least one of capacitive coupling and magnetic induction; the received power is shared among the third plurality of receiver resonators 50''

[1840] ; and the received power is presented in DC form from one or more of the third plurality of receiver resonators 50'' to the power load 70'' via wired communication through one or more corresponding receiver modules 40''. The method may further include converting a voltage and a current of the power from each photovoltaic cell 420 into a voltage and a current suitable for a corresponding transmission module 20'' before converting the power from each photovoltaic cell 420 into an oscillating power signal.

[0348] Figure 27A shows a representative portion 500 of an extended near-field wireless power distribution system in an electric vehicle having a conductive housing 510. In this embodiment of the general system 10′′ of Figure 19A, the power source is a rechargeable battery pack 520 instead of a solar cell 420 and the load 70′′ is an electric motor 530 instead of a battery pack as shown in Figure 19A. The system shown in Figure 14A may include a power conditioning unit 430 as shown in Figure 19A. In other embodiments, transmitter modules may work in conjunction to provide power conditioning, as explained above with reference to Figure 19B.

[0349] The system shown in Figure 27A and described in more detail below can operate by capacitive power transfer, inductive power transfer, or dual-mode power transfer. Referring to Figures 4B and 19A, the transmitter resonator 30′′ includes a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to Figures 4B and 19A, the receiver resonator 50′′ includes a dielectric element 158 ​​sandwiched between conductive antennas 152 and 154. The transmitter module 20′′ is shown mounted directly to antenna 132, which also serves as a frame or holder for battery pack 520. The transmitter module 20′′ can be electrically connected between battery pack 520 and transmitter resonator 30′′. The receiver module 40′′ is shown mounted directly to electric motor 530. The receiver module 40′′ can be electrically connected between receiver resonator 50′′ and motor 530.

[0350] Figure 27B shows a representative portion 500' of an extended near-field wireless power distribution system in an electric vehicle having a conductive housing 510. In this embodiment of the general system 10'' of Figure 19A, as in Figure 27A, the power source is again a rechargeable battery pack 520 instead of a solar cell 420 and the load 70'' is an electric motor 530 instead of a battery pack as shown in Figure 19A. The system shown in Figure 27B may include a power conditioning unit 430 as shown in Figure 19A. In other embodiments, the transmitter module 20'' and the receiver module 40'' may work together to provide power conditioning, as explained above with reference to Figure 19B.

[0351] The system shown in Figure 27B and described in more detail below can operate by capacitive power transfer, inductive power transfer, or dual-mode power transfer. Referring to Figures 4B and 19A, the transmitter resonator 30′′ includes a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to Figures 4B and 19A, the receiver resonator 50′′′ includes a dielectric element 158 ​​and a conductive antenna 152. In this embodiment, the antenna 154 of Figure 27A is not present in the resonator 50′′′. The transmitter module 20′′ is shown mounted directly to the antenna 132, which also serves as a frame or holder for the battery pack 520. The transmitter module 20′′ can be electrically connected between the battery pack 520 and the transmitter resonator 30′′. The receiver module 40′′ is shown mounted directly to the electric motor 530. In this embodiment, the receiver module 40′′ can be electrically connected between the motor 530 and the housing 510. In this configuration, there is sufficient coupling between the housing 510 and the antenna 152 for power transmission with appropriately high efficiency. The conductive mechanical components of the system (i.e., components in the system that have, for example, load-bearing structural functions) can thereby form part of the resonant structure of the power transmission system.

[0352] In the embodiments shown in Figures 27A and 27B, the focus is specifically on the power supplied to the electric motor 530 that drives one of the wheels of the vehicle, but a plurality of appropriately adapted receiver modules 40′′ (all powered by transmitter modules 20′′) can be used to implement an equivalent configuration for any electrical subsystem of the vehicle.

[0353] The configurations of Figures 27A and 27B for power transmission from a battery pack to the electrical subsystems of a vehicle largely eliminate the need for extremely complex automotive wiring harnesses, which cause difficulties during vehicle manufacturing and are a significant source of manufacturing costs. The embodiments in Figures 27A and 27B, together with their extensions to other electrical subsystems of the vehicle, can be described as an "extended near-field wireless power distribution system".

[0354] In addition to the other wheels of electric vehicles, this configuration can also be extended to headlights and other vehicle accessories, including (but not limited to) interior lights, instrument panel displays, gauges, digital electronics, navigation systems, warning systems, and the like. Applications are not limited to electric vehicles. It can be applied to hybrid or internal combustion engine vehicles to distribute power as needed. It can be similarly applied to other vehicles employing any electrical system that requires electricity. Examples include (but are not limited to) electric and non-electric bicycles, aircraft, boats, and other vehicles using onboard power. The battery pack or power source does not need to be onboard. The principles explained in Figures 1 to 11, 19A to 19B, and 27A to 27B also apply to stationary and vehicle systems that require power from a geostationary source (e.g., (but not limited to) a fixed track supplying power to a moving vehicle).

[0355] Figure 28A illustrates another embodiment of the general system 10′′ of Figure 19A in a power supply system 600, which supplies power from a suitable source to a computer monitor 610 positioned on a desktop 620 of a table via a primary side 12 according to Figure 1 (and more specifically, Figure 6). In system 600, both the transmitter module 20′′ and the transmission resonator 30′′ of Figure 19A are incorporated into the primary side 12. In the configuration of system 600, the receiver resonator 50′′ according to Figure 19A forms the substrate of monitor 610. The receiver module 40′′ of Figure 19A may be incorporated into the substrate of monitor 610. Alternatively, the receiver module 40′′ of Figure 19A may be incorporated into the monitor 610 itself. Referring to Figure 4B, antenna 152 forms the bottom of the substrate of monitor 610 and is separated from antenna 154 by dielectric 158.

[0356] The housing and structural frame 630 of the monitor 610 may be at least partially conductive and serve as a continuous conductor to supply power signals from antenna 154 to the circuitry of the monitor 610, representing the load resonator 70'' of FIG. 19A, via receiver module 40'' (see FIG. 19A). Other electrical connectors from antenna 152 to the circuitry of the monitor 610 extend from antenna 152 upwards to the base of the monitor 610. In other embodiments, the housing and structural frame 630 of the monitor 610 may be made of a non-conductive polymer, and a single conductor extends from antenna 154 to the circuitry of the monitor 610, representing the load resonator 70'' of FIG. 19A.

[0357] As shown in another embodiment of the power supply system 600' for supplying power to a computer monitor 610 in FIG28B, the substrate of the monitor 610 may consist only of the antenna 152 and the dielectric 158. In this embodiment, a metallic conductive portion of the monitor housing or frame 630 serves as the antenna instead of the antenna 154, and the housing or frame 630 has sufficient coupling to the antenna 152 below the dielectric 158 to provide sufficiently efficient power transmission. The receiver module 40'' of FIG19A may be incorporated into the substrate of the monitor 610. Alternatively, the receiver module 40'' of FIG19A may be incorporated into the monitor 610 itself. The housing and structural frame 630 of the monitor 610 may serve as a continuous electrical conductor to supply a power signal via the receiver module 40'' to the circuitry of the monitor 610, which represents the load resonator 70'' of FIG19A.

[0358] System 600 may include a power conditioning unit 430 as shown in FIG19A. In some embodiments, transmitter module 20′′ and receiver module 40′′ may work together to provide power conditioning as explained with reference to FIG19A, although near-field wireless power transmission is used. The near-field wireless power transmission system of FIG28A eliminates the need for bulky power cables to supply power to monitor 610 and uses the system's mechanical structural elements as an integrated electrical / electronic component in the power transmission configuration.

[0359] Referring to the flowchart in FIG29 and the system descriptions in FIG19A and FIG19B, a method

[2000] is provided for transmitting power from a DC power source 420 to a power load 70′′, the method comprising:

[2010] providing a power transmission system 10′′, 410 in wired communication with the power source 420, the power transmission system 10′′, 410 including an oscillator 26A′′ capable of oscillating at an oscillation frequency; a power amplifier 26B′′ and a transmitter tuning network 28′′, both under the control of a transmitter controller 22′′; and a receiver tuning network 48′′ and a load management system 46E′′, both under the control of a receiver controller 42′′, wherein the load management system 46E′′ and the power load 70′′ are connected. The system includes wired communication; converting power from power source 420 into an oscillating power signal with an oscillation frequency in power amplifier 26B′′; transmitting the power signal from power amplifier 26B′′ to load management system 46E′′ via transmitter tuning network 28′′ and receiver tuning network 48′′ under the control of transmitter controller 22′′; adjusting at least one of the oscillation frequency, one input DC equivalent resistance of power amplifier 26B′′, transmitter tuning network 28′′, receiver tuning network 48′′ and load management system 46E′′ to change a power transmission rate; and presenting the power received by load management system 46E′′ in DC form via wired communication to power load 70′′.

[0360] The power signal transmitted via the transmitter tuning network 28′′ and the receiver tuning network 48′′

[2030] may include power transmission via wired communication or wireless communication. Power transmission via wireless communication may include power transmission via near-field wireless communication. Power transmission via near-field wireless communication may include power transmission via at least one of capacitive coupling and inductive coupling. Power transmission from DC power source 420 may include power transmission from at least one solar cell 420. Power transmission from DC power source may include power transmission from at least one battery pack. Power transmission from DC power source may include power transmission from a power source having a different voltage.

[0361] In another embodiment, referring to the flowchart in FIG30 and more specifically to the system description of FIG19A and FIG19B, a method

[2100] is provided for transmitting power from a DC power source 420 to a power load 70′′, the method comprising:

[2110] providing a power transmission system 10′′, 410 in wired communication with the power source 420, the power transmission system 10′′, 410 including an adjustable phase radio frequency rectifier 46D (See Figure 7) One aspect of radio frequency communication is a radio frequency power amplifier 26B′′, which has an adjustable phase radio frequency rectifier 46D in wired contact with a power load 70′′; in the amplifier 26B′′, power from a DC power supply 420 is converted

[2120] into a radio frequency oscillating power signal; in the rectifier 46D, the radio frequency oscillating power signal is converted

[2130] into a DC power signal; and the efficiency of power transmission is adjusted

[2140] by adjusting a current-voltage phase characteristic of the rectifier 46D. Providing an adjustable phase radio frequency rectifier may include providing a differential self-synchronizing radio frequency rectifier 46D.

[0362] The method

[2100] may further include adjusting the efficiency of power transmission by adjusting one of the DC equivalent input resistances of amplifier 26B′′.

[2110] The power transmission systems 10′′, 410 may include a load management system 46E′′ providing wired communication between rectifier 46D and load 70′′. Adjusting the DC equivalent input resistance of amplifier 26B′′ may include adjusting one of the input impedances of rectifier 46D by adjusting the load management system 46E′′. Adjusting the load management system 46E′′ may include automatically adjusting the load management system 46E′′.

[0363] The method

[2100] may further include adjusting the efficiency of power transmission by adjusting the current-voltage phase characteristics of one of the power amplifiers 26B′′.

[2110] The power transmission systems 10′′, 410 may include providing a transmitter controller 22′′ that communicates with the power amplifiers 26B′′ to control them. Adjustment of the current-voltage phase characteristics of the power amplifiers 26B′′ may be performed by the transmitter controller 22′′. Adjustment of the current-voltage phase characteristics of the power amplifiers 26B′′ may be performed automatically by the transmitter controller 22′′.

[0364] The method

[2100] may further include adjusting the efficiency of power transmission by changing the oscillation frequency of one of the power amplifiers 26B′′.

[0365] The power transmission system 10′′, 410 provided

[2110] may include a receiver controller 42′′ that communicates with the rectifier 46D to control the rectifier 46D. Adjustment of the current-voltage phase characteristics of the rectifier 46D may be performed by the receiver controller 42′′. Adjustment of the current-voltage phase characteristics of the rectifier 46D may be performed automatically by the receiver controller 42′′.

[0366] The

[2110] power transmission systems 10′′, 410 may include a power amplifier 26B′′ that provides direct wired radio frequency communication (via connection 60′′ of FIG. 19B) with the adjustable phase radio frequency rectifier 46D. The

[2110] power transmission systems 10′′, 410 may include a power amplifier 26B′′ that provides wireless near-field radio frequency communication with the adjustable phase radio frequency rectifier 46D.

[0367] The

[2110] power transmission system 10′′, 410 may include a transmitter resonator 30′′ providing wired radio frequency communication with power amplifier 26B′ and a receiver resonator 50′′ providing wired radio frequency communication with radio frequency rectifier 46D. The method

[2100] may further include the transmitter resonator 30′′ and receiver resonator 50′′ operating each other in wireless near-field radio frequency communication. The

[2110] power transmission system 10′′, 410 may include a power amplifier 26B′′ providing at least one of capacitive near-field wireless radio frequency communication and inductive near-field wireless radio frequency communication with rectifier 46D. The

[2110] power transmission system 10′′, 410 may include a power amplifier 26B′′ providing dual-mode wireless near-field communication with rectifier 46D.

[0368] The method

[2100] may further include: providing a power conditioning unit 430 electrically disposed between the power source 420 and the power transmission system 10′′; and adjusting the power conditioning unit 430 to adjust at least one of a current and a voltage from the power source 420 to improve the efficiency of power transmission.

[0369] Based on a further consideration of the systems of Figures 19A and 19B and referring to Figure 7, a generalized power transmission system 10′′, 410 for supplying power from a DC power source 420 to a power load 70′′ includes: a radio frequency power amplifier 26B′′ which is wired to the power source 420 and configured to convert the DC voltage from the power source 420 into an AC voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier which is wired to the power load 70′′ and radio frequency to the power amplifier, the rectifier being configured to receive power transmitted from the power amplifier 26B′′; and a receiver controller 42′′ which communicates with the rectifier 46D, the receiver controller being configured to adjust the efficiency of power transmission from the power amplifier 26B′′ to the rectifier 46D by adjusting a current-voltage phase characteristic of the rectifier 46D. The receiver controller 42′′ can be configured to automatically adjust the current-voltage phase characteristics of the rectifier 46D. The rectifier can be a differential self-synchronizing RF rectifier.

[0370] The power transmission systems 10′′ and 410 may further include a load management system 46E′′ that is wired to the load 70′′ and whose power signal is disposed between the load 70′′ and the rectifier 46D. The load management system 46E′′ is configured to increase the efficiency of power transmission by adjusting an input impedance of the rectifier 46D. The load management system 46E′′ may be configured to automatically adjust the input impedance of the rectifier 46D.

[0371] The power transmission systems 10′′ and 410 may further include a transmitter controller 22′′ that communicates with the amplifier 26B′′. The transmitter controller 22′′ is configured to increase the efficiency of power transmission by adjusting the current-voltage phase characteristics of the amplifier 26B′′. The transmitter controller 22′′ can be configured to automatically adjust the current-voltage phase characteristics of the amplifier 26B′′ to increase the efficiency of power transmission.

[0372] The power transmission systems 10′′ and 410 may further include an oscillator 26A′′ that communicates with the amplifier 26B′′ and the transmitter controller 22′′. The transmitter controller 22′′ may be configured to adjust the oscillation frequency via the oscillator 26A′′.

[0373] Power amplifier 26B′′ can communicate directly via wired radio frequency (RF) with adjustable phase RF rectifier 46D (via connection 60′′ in FIG. 19B). Power amplifier 26B′′ can also communicate wirelessly with adjustable phase RF rectifier 46D in the near field. Power transmission systems 10′′, 410 may include a transmitter resonator 30′′ communicating via wired RF with power amplifier 26B′′ and a receiver resonator 50′′ communicating via wired RF with rectifier 46D. Transmitter resonator 30′′ and receiver resonator 50′′ can communicate wirelessly with each other in the near field. Power amplifier 26B′′ can communicate with rectifier 46D via at least one of capacitive or inductive near field wireless communication. Power amplifier 26B′′ can communicate with rectifier 46D in a dual-mode near field wireless communication.

[0374] The power transmission system may further include a power conditioning unit 430 electrically disposed between the power supply 420 and the power amplifier 26B′′, the power conditioning unit 430 being configured to adjust at least one of a current and a voltage from the power supply 420 to improve the efficiency of power transmission.

[0375] In another embodiment described with reference to Figures 19A, 19B, 27A and 27B, and 28A and 28B, an electric system includes: a mechanical load-bearing structure 510, 630 having a conductive first portion; an electrical load; and a power transmission system 10′′, 410 including at least one radio frequency resonator 30′′, 50′′ configured for near-field wireless power transmission, wherein the resonator at least partially includes the conductive first portion. The electric system may further include a rechargeable battery pack 520 and the electrical load may include an electric motor 530. The electric system may be an electric vehicle 500, 500′ and the mechanical load-bearing structure may include a vehicle housing 510. The electric system may be a display monitor 610 and the mechanical load-bearing structure may be at least one of a frame 630 and a monitor substrate.

[0376] The electric system may further include a power source. The power transmission system may include: a radio frequency power amplifier 26B′′ that is wired to the power source and configured to convert a DC voltage from the source into an AC voltage signal having an oscillation frequency; an adjustable phase radio frequency rectifier 46D that is wired to the power load 70′′ and radio frequency to the power amplifier 26B′′, the rectifier 46D being configured to receive power transmitted from the amplifier 26B′′; and a receiver controller 42′′ that communicates with the rectifier 46D, the receiver controller 42′′ being configured to adjust the efficiency of power transmission from the amplifier 26B′′ to the rectifier 46D by adjusting a current-voltage phase characteristic of the rectifier 46D.

[0377] In another embodiment depicted in Figures 19A and 19B, 27A and 27B, and 28A and 28B, a device includes: a mechanical load-bearing structure 510, 630 having a conductive first portion; a power source; an electrical load 70′′, 530, 610; and a power transmission system 10′′, 410, including: a radio frequency power amplifier 26B′′ wiredly communicating with the power source and configured to convert a DC voltage from the source into an AC voltage signal having an oscillation frequency; and an adjustable phase radio frequency rectifier 4. A rectifier 46D is wired to a power load 70′′ and communicates with a power amplifier 26B′′ via radio frequency. The rectifier 46D is configured to receive power transmitted from the amplifier 26B′′. A receiver controller 42′′ communicates with the rectifier 46D and is configured to adjust the efficiency of power transmission from the amplifier 26B′′ to the rectifier 46D by adjusting a current-voltage phase characteristic of the rectifier 46D. The conductive first portion is positioned to carry at least one radio frequency signal from the amplifier 26B′′ and the rectifier 46D.

[0378] The device may further include a load management system 46E'' that is wired in communication with the load 70'' and electrically located between the load 70'' and the rectifier 46D. The load management system 46E'' is configured to increase power transmission efficiency by adjusting an input impedance of the rectifier 46D. The device may further include a transmitter controller 22' that communicates with the amplifier 26B''. The transmitter controller 22' is configured to increase power transmission efficiency by adjusting a current-voltage phase characteristic of the amplifier 26B''. The device may further include an oscillator 26A'' that communicates with the amplifier 26B'' and the transmitter controller 22', wherein the transmitter controller 22' is configured to adjust the oscillation frequency via the oscillator 26A''.

[0379] The power amplifier 26B′′ can communicate directly with the rectifier 46D via a conductive first portion via wired radio frequency (RF). The power amplifier 26B′′ can also communicate wirelessly with the rectifier 46D via near-field radio frequency (NFC). The power transmission systems 10′′ and 410 may include a transmitter resonator 30′′ communicating with the power amplifier 26B′′ via wired RF and a receiver resonator 50′′ communicating with the rectifier 46D via wired RF, and one of the transmitter resonator 30′′ and the receiver resonator 50′′ may include a conductive first portion. The transmitter resonator 30′′ and the receiver resonator 50′′ can communicate wirelessly with each other via NFC. The power amplifier 26B′′ can communicate with the rectifier 46D via at least one of capacitive NFC and inductive NFC. The power amplifier 26B′′ can communicate with the rectifier 46D via dual-mode NFC. The DC power supply may include a rechargeable battery pack 520 and the load may include an electric motor 530.

[0380] In a further embodiment schematically shown in FIG. 32 and based on one of FIG. 6, 7, 8 and 9, a sealed bidirectional power transmission circuit device 800 is provided, having a plurality of terminals disposed for electrical communication with devices outside the sealed device 800. The sealed device 800 includes within its sealed interior a multi-terminal power switching (MPS) device 810 having at least one DC terminal, at least one AC terminal and at least one control terminal. The MPS device 810 is adjustable between an amplification state and a rectification state and is configured to bidirectionally transmit a DC voltage and a DC voltage via at least one DC terminal. A current is transmitted bidirectionally via at least one AC terminal to a radio frequency power signal having an amplitude, a frequency, and a phase; a phase, frequency, and duration cycle adjustment (PFDCA) circuit 820 is wiredly data-communicating with a controller 880 and wiredly electricalally communicating with an MPS device 810 via at least one control terminal. The PFDCA circuit 820 is configured to establish a radio frequency oscillation signal having the frequency and phase of the radio frequency power signal at at least one control terminal of the MPS device 810 and to adjust the MPS device 810 between an amplification state and a rectification state by adjusting the phase of the radio frequency oscillation signal under the command of the controller 880. The PFDCA circuit 820 may be further configured to establish a duration cycle of the radio frequency oscillation signal. The PFDCA circuit 820 may include a radio frequency oscillator for generating the radio frequency oscillation signal under the command of the controller 880. The term "multi-terminal power switching device" is used herein to describe a device having at least three terminals and capable of switching or modulating a current flowing between at least two terminals of the device based on a signal applied to at least one third terminal of the device. Suitable MPS devices 810 include (but are not limited to) mechanical relay switches, solid-state switches, electro-optic switches (also known as optical switches), thyristors, waveguide switches, transistors (including, for example, MOSFETs, MESFETs, III to V group semiconductor transistor devices and BJT devices) and power transistor devices (including, for example, triodes and pentodes).

[0381] In some embodiments, the circuit is sealed or molded using a polymer coating to create a sealed or sealed device. In some embodiments, the sealed device protects components disposed inside one of the devices. In some embodiments, the seal of the device provides electrical insulation to prevent electrostatic discharge, short circuits, or other harmful discharges that could damage components of the device. In some embodiments, the sealed device protects internal components from oxidation. In some embodiments, the seal may create a water-proof barrier or a water vapor barrier. In some embodiments, the seal provides facilitating electrical connection to one of the devices by providing access to one or more terminals on the exterior of one of the sealed devices.

[0382] The hermetically sealed power transmission circuit device 800 may further include, within the hermetically sealed interior, a tuning network 830 that communicates with the controller 880 via wired data communication and with the MPS device 810 via at least one AC terminal. The tuning network 830 is configured to adjust the radio frequency power signal to a tuned radio frequency power signal from the tuning network 830 upon instruction from the controller 880 when the MPS device 810 is in amplification mode. The tuning network 830 may include a harmonic termination network circuit of the type shown in Figures 8 and 9, configured to suppress harmonics of radio frequency oscillation signals in the radio frequency power signal. As shown in Figures 8 and 9, the harmonic termination network may include one or more inductors and one or more of the first harmonic terminals 127I, 147G, the second harmonic terminals 127H, 147F, and the third harmonic terminals 127F, 147D.

[0383] The hermetically sealed power transmission circuit device 800 may include, within its hermetically sealed interior, an amplitude / frequency / phase detector (AFPD) 840 that communicates wiredly with a controller 880. The AFPD 840 is configured to communicate wiredly with a tuning network and to determine the amplitude, frequency, and phase of any radio frequency power signal transmitted between the tuning network and an AC load / source outside the hermetically sealed device. For this purpose, according to FIG. 32, the AFPD 840 measures the signal amplitude, frequency, and phase at the output of the tuning network 830 derived from the device 800. A PFDCA circuit 820 is configured to receive instructions from the controller 880 based on the measurement data transmitted to the controller 880 via the AFPD 840. In other embodiments not shown in FIG. 32, the PFDCA circuit 820 is configured to adjust at least one of the radio frequency oscillation signal and / or DC current and DC voltage based on a feedback signal received directly from the AFPD 840.

[0384] The tuning network 830 may include a voltage-current tuner for adjusting a phase difference between a voltage and a current of a tuned radio frequency signal based on measurement data from the AFPD 840 when the power switching device is in amplification mode. A suitable voltage-current tuner is described in detail with reference to FIG6. According to FIG32, the voltage-current tuner of the tuning network 830 is applied to a signal designated for a signal connection derived from device 800. It thereby functions as a tuner when power is transmitted downward through FIG32. The voltage-current tuner may be transparent to power transmitted in the opposite upward direction through device 800 in FIG32, and the power transmission circuit device 800 is bidirectional. In some embodiments, the tuning network 830 may transmit a tuned radio frequency power signal to an AC load / source 900, which may be a transmitter resonator 30 and 30'', as described with respect to FIG6 and FIG19A, FIG27A and FIG27B. When the AC load / source 900 is a dual-mode transmitter resonator, the voltage-current tuner can be used to adjust the ratio of the electric field to the magnetic field, as described with respect to Figure 6.

[0385] The hermetically sealed power transmission circuit device 800 may further include, within its hermetically sealed interior, a power management (PM) circuit 860 that communicates wiredly with the controller 880 and wiredly with the MPS 810 and an external DC power supply / load 700. The PM circuit 860 is configured to impedance match the MPS 810 and the external DC power supply / load 700 and to adjust the DC power transmitted between the MPS 810 and the DC power supply / load 700 based on measurement data transmitted to the controller via the AFPD 840. In other embodiments not shown in FIG32, the PM circuit 860 may be configured to adjust the DC power transmitted between the MPS 810 and the DC power supply / load 700 based on a feedback signal received directly from the AFPD 840 and / or the VID 850.

[0386] It should be noted again that DC power can be transmitted in both directions between the MPS 810 and the DC power supply / load 700 via the PM circuit 860. It should also be noted that we maintain the convention here of describing the DC power supply / load 700 as a "source / load" and the external AC load / source 900, which transmits AC power to the tuning network, as a "load / source," to emphasize that when the DC power supply / load 700 is used as a DC power source, the AC load / source 900 is used as a load for that power being converted to AC power, and vice versa. The arrows depicted near and parallel to the connector in Figure 32 indicate the path and direction of the power flow through device 800 when the MPS 810 is in either its amplification or rectification state. When the MPS 810 is in its amplification state, the power flow is downward through Figure 32; when the MPS 810 is in its rectification state, the power flow is upward through Figure 32.

[0387] The hermetically sealed power transmission circuit device 800 may further include, within its hermetically sealed interior, a voltage / current sensor (VID) 850 that communicates with the controller 880 via wired data. The VID 850 is configured to determine a DC voltage and DC current transmitted between the MPS 810 and the PM circuit 860. When the MPS 810 is in amplification mode, the power transmission circuit device 800 can be adjusted based on the measurement of the VID 850 such that the device 800 presents an equivalent DC load to the DC source / load 700, thereby allowing maximum power extraction from the DC source / load 700. This adjusts the DC voltage at at least one DC terminal of the MPS device 810. When the MPS 810 is in rectification mode, the power transmission circuit device 800 can be adjusted based on the measurement of the VID 850 such that the device 800 presents an equivalent DC source impedance to the DC source / load 700, thereby allowing maximum power transmission from the device 800 to the DC source / load 700. This adjusts the DC voltage at one of the wired connections between device 800 and DC source / load 700.

[0388] The hermetically sealed power transmission circuit device 800 may further include, within its hermetically sealed interior, a memory 870 that communicates with the controller 880, the AFPD 840, and the VID 850 via wired data communication. The memory 870 is configured to receive and store signal data from the two detectors 840 and 850 and to provide the signal data from the two detectors 840 and 850 to the controller 880. The memory 870 may be able to store the complete state of a series of continuous transient time-series devices 800.

[0389] The tuning network may further include one or more of a compensation network, a matching network, and a filter. The compensation network 26E, matching network 26D, and filter 26C of Figure 6 are suitable for this purpose, and the choice is not limited to the devices in Figure 6.

[0390] The hermetically sealed power transmission circuit device 800 may include a controller 880 within its hermetically sealed interior. In other embodiments, the hermetically sealed power transmission circuit device 800 may employ an external controller having suitable input / output facilities to communicate data with various circuit systems incorporated within the hermetically sealed interior of the device 800, and suitable software or firmware that can be programmed into the controller to execute all the control procedures described above.

[0391] The hermetically sealed power transmission circuit device 800 may further include at least one communication circuit 890 that operates on one or more of Bluetooth, WiFi, Zigbee, and cellular technologies to bidirectionally transmit information between the controller 880 and devices external to the hermetically sealed power transmission circuit device 800. The at least one communication circuit 890 may communicate bidirectionally with one or more suitable antennas 894. While one or more antennas 894 may be housed within the hermetically sealed interior of the device 800, they are generally more usefully housed externally to the device 800. One or more external devices may be other power transmission circuit devices (including, for example, other devices 800), and one or more other devices may form part of a common power transmission system as explained above in other embodiments (e.g., FIG. 1).

[0392] The PFDCA circuit can be configured to adjust the duration cycle of the radio frequency oscillation signal based on measurements from AFPD 840 and VID 850. In some embodiments, measurement information can be transmitted to controller 880 and from there to PFDCA circuit 820, which then adjusts the duration cycle of the radio frequency oscillation signal based on the received information. In other embodiments not shown in FIG32, a feedback signal can be directly transmitted from AFPD 840 and VID 850 to PFDCA circuit 820, which then adjusts the duration cycle of the radio frequency oscillation signal based on the received feedback signal. By changing the duration cycle of the radio frequency oscillation signal, PFDCA circuit 820 can adjust the direction of the power flowing through device 800. When power flows from DC source / load 700 through device 800 to AC load / source 900, PFDCA circuit 820 can thereby adjust the DC power delivered to device 800 via source / load 700 and the AC power delivered from device 800 to AC load / source 900. When power flows from AC load / source 900 through device 800 to DC source / load 700, PFDCA circuit 820 can thereby adjust the AC power delivered to device 800 via AC load / source 900 and the power delivered from device 800 to DC source / load 700.

[0393] The controller 880 can communicate bidirectionally with external devices and circuitry 898 (labeled as external (Ext.) in FIG. 32) located inside or outside the sealed interior of the device 800. This wired communication can be used to (e.g., but not limited to) exchange data or supply the controller 880 with a clock synchronization signal for one of the systems into which the device 800 can be incorporated.

[0394] Referring to Figures 6 and 7, sensors and detectors 24A, 24B, 24C and 24D can be usefully disposed outside the sealed interior of device 800.

[0395] The bidirectional power transmission circuit device 800 can also be usefully used to transmit and / or receive information via the power channel of device 800 through the mechanism already explained above with reference to Figures 6 and 7. The power channel extends from the wired connection between the DC source / load 700 and the PM circuit 860 through the PM circuit 860, VID 850, MPS device 810, and tuning network 830 to the AC load / source 900. Along the physical power channel, the PM circuit 860, MPS device 810, and tuning network 830 are all under the control of controller 880, which controls MPS device 810 via PFDCA circuit 820. The controller can modulate the radio frequency power signals in the tuning network 830 and / or MPS device 810 itself. The controller can also be configured to trigger modulation of the DC voltage between the PM circuit 860 and the DC source / load 700. This allows information to be modulated on a radio frequency power signal, a tuned radio frequency power signal, and / or the aforementioned DC voltage, and thereby transmitted to other devices outside device 800. These other devices may include further bidirectional power delivery circuitry device 800. Information can be modulated digitally or analogously onto the radio frequency power signal, the tuned radio frequency power signal, and / or the aforementioned DC voltage. In other embodiments, information can be modulated to a frequency different from the power delivery frequency. In other embodiments, information can be modulated to a harmonic of the power signal frequency. In yet another embodiment, the frequency of the radio frequency power signal can be a harmonic of the frequency of the signal to which the information is modulated. In the description above, we have explained how the subsystem of the tuning network 830 can be used as a suitable modulator.

[0396] The foregoing has described how device 800 can be reconfigured between transmitter mode and rectifier mode, and how the power channel can be modulated. Clearly, device 800 can be used as a full-duplex transmit-receive system for transmitting information in one of two directions. When two devices 800 are used in modules 20 and 40 of FIG. 1, system 10 of FIG. 1 may include a further secondary side similar to the secondary side 14 of FIG. 1. When an additional secondary side 14 is present, the configuration described above allows information to be communicated in the various secondary sides 14 and thereby with the primary side 12. By using device 800 of FIG. 32, the same full-duplex transmit-receive configuration is feasible in the transmitter module 20'' and receiver module 40'' used in the systems of FIG. 19A and FIG. 19B. The same is true for the systems shown in FIG. 20A to 22B and FIG. 27A to 28B.

[0397] The information transmitted in the manner described herein may include (but is not limited to) the operating mode of the MPS device 810, the number and type of further devices 810, surrounding object sensor information and load status monitoring information (including, for example, battery pack charge status, load voltage and load current).

[0398] The electronic circuitry of the hermetically sealed bidirectional power transmission circuit device 800 can be implemented using various device manufacturing techniques as (including, but not limited to) a plurality of discrete devices suitable for a circuit board, wherein devices manufactured from different individual segments of semiconductor material can be bonded or mounted to a hybrid circuit on a suitable substrate material, active-side down bonded to one or more individual devices in a flip-chip configuration on a silicon-based circuit, or a single monolithic integrated circuit device. Figure 33 illustrates a flip-chip configuration of a multi-terminal power switching (MPS) device 810 implemented in a single semiconductor crystal and then flip-chip mounted on a pad 808 via solder bumps. The MPS device 810 can, for example (but not limited to), be manufactured as a discrete higher-power device in a wide-bandgap semiconductor crystal. The pad 808 is fabricated on a silicon wafer 801, which also contains a balance of all subsystems of the device 800 of Figure 32 monolithically integrated within the wafer 801. The two pads 806 are used to connect to devices 700 and 900 shown in Figure 32. The pad 802 is used to connect the controller 880 and communication circuit 890 to devices and antennas outside of device 800.

[0399] In one particular embodiment shown in FIG34A, the electronic circuitry of the sealed bidirectional power transmission circuit device 800 may be implemented in conjunction with at least one photovoltaic cell 814 serving as the DC source / load 700 of FIG32 within a single silicon single crystal wafer 812.

[0400] In a further embodiment further explained with reference to FIG. 34B, the electronic circuitry of the hermetically sealed bidirectional power transmission circuit device 800 may be implemented together with a resonator structure 180', of the type described with reference to FIG. 2B and described in more detail with respect to FIGS. 2A to 5, serving as an AC load / source 900 on one surface of a silicon single-crystal wafer 812, as described above, in conjunction with at least one photovoltaic cell 814 serving as a DC source / load 700 of FIG. 32, within the single silicon single-crystal wafer 812. An antenna 894 for use with Bluetooth, WiFi, Zigbee, and cellular technologies may also be integrated on the same single silicon single-crystal wafer. The antenna 894 is not shown in FIG. 34B. In FIGS. 34A and 34B, connection 818 connects the resonator 180' and the tuning network 830 of the device 800. The resonator 180' may be used as a heat sink or heat radiator for heat generated in the device 800 or absorbed by the photovoltaic cell 814. For this purpose, the resonator 180' can use air as a dielectric and simultaneously as a coolant fluid.

[0401] In other embodiments, the DC load 70′′ of Figures 19A and 19B is replaced by an AC load 70′′′ in the two cases shown in Figures 35A and 35B, respectively. The remainder of systems 10′′ and 410 of Figures 35A and 35B may be the same as systems 10′′ and 410 of Figures 19A and 19B. The oscillator 26A′′ of Figures 19A and 19B may be set to the frequency and phase required by the AC load 70′′′ of Figures 19A and 19B. In other embodiments, the transmitter controller 22′′ may be programmed to set the oscillator 26A′′ to the frequency and phase required by the AC load 70′′′.

[0402] In another embodiment of the systems of Figures 35A and 35B, the AC load 70′′′ may be configured by the systems of Figures 35A and 35B to deliver power to one of their power grids. In these power grid supply configurations, controlling the frequency, phase, and voltage level of the signals fed from the systems of Figures 35A and 35B to the power grid 70′′′ is important. For this purpose, the information feedback mechanism described above can be used to transmit information about the required frequency, phase, and voltage level of the power grid back to the transmitter controller 22′′. This information may be in digital or analog form. In some embodiments of the wired system of Figure 35B, an additional signal line (not shown to avoid clutter) may be taken from the AC power grid 70′′′ to the transmitter controller 22′′ or directly to the oscillator 26A′′ to allow the transmitter module 20′′ to directly track the AC load with respect to frequency and phase, thereby imposing the constraints required by the power grid 70′′′ on the output signal of the system of Figure 35B. These constraints may include modulation of the output signal of the load management system 46E′′ to meet the requirements of the power grid 70′′′. The modulation may be at a frequency equal to the frequency of the power grid and at a phase and voltage level that transmits power to the power grid 70′′′.

[0403] Figure 36 illustrates one embodiment of the system of Figure 32, where the AC load / source 900 is an AC power grid 900'. In this embodiment, as with the systems of Figures 35A and 35B, information regarding the required frequency, phase, and voltage level of the power grid can be transmitted back to the controller 880. This allows the controller 880 to adjust the signal at the control terminal of the MPS device 810 via the phase, frequency, and duration-of-action (PFDCA) circuit 820 to meet the power delivery requirements imposed by the power grid 900'. These requirements may include modulation of the output signal of the tuning network 830 to meet the requirements of the power grid 70'''. The modulation may be at a frequency equal to the frequency of the power grid and at a phase and voltage level for delivering power to the power grid 70'''. Although inherently bidirectional, the system of Figure 36 can be configured thereby as a means for delivering power to an AC power grid.

[0404] Returning now to Figures 20A and 20B, 21A and 21B, and 22A and 22B, each solar cell 420 may be equipped with a sensor to determine the operating state of the solar cell 420. The operating state may include (but is not limited to) power level, voltage level, current level, temperature, and other performance parameters. This information regarding the operating state may be transmitted to a receiver module 40'' via a plurality of transmitter modules 20'' associated with (a plurality of) solar cells 420. The operating state of (a plurality of) transmitter modules 20'' may similarly be sensed and transmitted to the receiver module 40'' via the transmitter modules 20''. Referring to Figures 33 and 34A and 34B, suitable sensors may also sense performance parameters via a sealed bidirectional power transmission circuit device 800 and a multi-terminal power switching (MPS) device 810. The transmission of load information via the MPS device 810 has already been described. Information regarding the performance parameters of devices 800 and 810 can be similarly transmitted through the system of this invention.

[0405] Although several exemplary embodiments and examples have been discussed above, those skilled in the art will recognize certain modifications, arrangements, additions, and sub-combinations thereof. Therefore, the claims described below in the appended claims and subsequent descriptions are interpreted to include all such modifications, arrangements, additions, and sub-combinations as consistent with the broadest interpretation of the specification as a whole. Interpretation of Terms

[0406] Unless otherwise explicitly required by the background information, this applies throughout the description and the scope of the invention application:

[0407] The words “comprise / comprising” and similar terms should be interpreted as inclusive rather than exclusive or exhaustive; that is, “includes, but is not limited to”.

[0408] Any variation of “connection”, “coupling” or the like means any direct or indirect connection or coupling between two or more elements; the coupling or connection between elements may be physical, logical or a combination thereof; elements formed integrally may be considered as connected or coupled;

[0409] “wired”, “via a wired connection” or any variation thereof means any physical connection via a conductive medium, intermediate circuit or other means, thereby allowing the flow of a current between, through or across the components of a system;

[0410] "Electrical communication" or any variation thereof means any connection, coupling, interface or other means applicable to the transmission of an electrical signal between, through or across components of a system for communication (wired, wireless or a combination thereof);

[0411] When the words “in this document”, “above”, “below” and similar terms are used to describe this specification, they shall refer to this specification as a whole and not to any specific part thereof;

[0412] The word "or" in the list of two or more items encompasses all of the following interpretations: any of the items in the list, all of the items in the list, and any combination of the items in the list;

[0413] The singular forms “a / an” and “the” also include the meaning of any appropriate plural form.

[0414] The directional terms used herein and in any of the appended claims (where applicable) such as “vertical,” “lateral,” “horizontal,” “up,” “down,” “forward,” “backward,” “inward,” “outward,” “left,” “right,” “front,” “back,” “top,” “bottom,” “below,” “above,” “under,” and the like depend on the specific orientation of the described and illustrated device. Various alternative orientations may be assumed for the subject matter described herein. Therefore, these directional terms are not strictly defined and should not be interpreted narrowly.

[0415] Embodiments of the present invention include the various operations described herein. These operations can be performed by hardware components, software, firmware, or a combination thereof.

[0416] Some embodiments may be implemented as a computer program product that may include instructions stored on a machine-readable medium. These instructions may be used to program a general-purpose or special-purpose processor to perform the operations. A machine-readable medium includes any means (e.g., software or a processing application) for storing information in a form readable by a machine (e.g., a computer). Machine-readable media may include (but are not limited to) magnetic storage media (e.g., floppy disks); optical storage media (e.g., CD-ROMs); magneto-optical storage media; read-only memory (ROM); random access memory (RAM); erasable programmable memory (e.g., EPROM and EEPROM); flash memory; or another type of media suitable for storing electronic instructions.

[0417] Additionally, some embodiments may be implemented in a distributed computing environment in which machine-readable media are stored on more than one computer system and / or executed by more than one computer system. Furthermore, information transmitted between computer systems may be retrieved or pushed across communication media connecting the computer systems.

[0418] Computer processing components used to implement various embodiments of the present invention include one or more general-purpose processing devices, such as a microprocessor or central processing unit, a controller, a graphics processing unit (GPU), a cellular computer, or the like. Additionally, such digital processing components may include one or more special-purpose processing devices, such as a digital signal processor (DSP), an application-specific integrated circuit (ASIC), a field-programmable gate array (FPGA), or the like. In a particular embodiment, for example, the digital processing device may be a network processor having one of multiple processors including a core unit and multiple microengines. Furthermore, the digital processing device may include any combination of (a plurality of) general-purpose processing devices and (a plurality of) special-purpose processing devices.

[0419] Although the operations of (some) methods herein are shown and described in a particular order, the order of operations of each method may be changed so that some operations may be performed in reverse order or so that some operations may be performed at least partially concurrently with other operations. In another embodiment, instructions or sub-operations of dissimilar operations may be presented in a discontinuous and / or alternating manner.

[0420] In the case of a component (e.g., a software module, processor, assembly, device, circuit, etc.) mentioned above, unless otherwise indicated, the reference to such component (including a reference to a "means") shall be interpreted as including any component that performs the function of said component as an equivalent of that component (i.e., functionally equivalent), including components that are not structurally equivalent to the disclosed structure but perform the function of the illustrated exemplary embodiments of the invention.

[0421] Specific examples of systems, methods, and apparatuses have been described herein for illustrative purposes. These are merely examples. The techniques provided herein are applicable to systems other than the exemplary systems described above. Many changes, modifications, additions, omissions, and arrangements are possible within the practice of this invention. This invention includes variations to the described embodiments that will be appreciated by those skilled in the art, including variations obtained by: replacing features, elements, and / or actions with equivalent features, elements, and / or actions; mixing and matching features, elements, and / or actions from different embodiments; combining features, elements, and / or actions from embodiments as described herein with features, elements, and / or actions from other techniques; and / or omitting combinations of features, elements, and / or actions from the described embodiments. [Simplified Explanation of the Diagram]

[0103] Exemplary embodiments are depicted in the reference figures of the drawings. The embodiments and figures disclosed herein are intended to be illustrative rather than limiting.

[0104] Figure 1 is a schematic diagram of a wireless power transmission system according to one of the exemplary embodiments.

[0105] Figures 2A, 2B and 2C depict antennas that can be used in various exemplary embodiments, either alone or in combination with other disclosed elements.

[0106] Figures 3A and 3B depict side profile views of antennas that can be used in various exemplary embodiments, either alone or in combination with other disclosed elements.

[0107] Figures 4A, 4B, 4C and 4D depict side profile views of exemplary resonators that can be used alone or in combination with other disclosed elements in various exemplary embodiments.

[0108] Figure 5 depicts a cross section of an exemplary resonator that can be used alone or in combination with other disclosed elements in various exemplary embodiments.

[0109] Figure 6 is a schematic depiction of a primary side of a wireless power transmission system according to an exemplary embodiment.

[0110] Figure 7 is a schematic depiction of a primary side of a wireless power transmission system according to one of the exemplary embodiments.

[0111] FIG8 is a schematic depiction of one of the exemplary power amplifiers that can be used alone or in combination with other disclosed elements in various exemplary embodiments.

[0112] FIG9 is a schematic depiction of one of the exemplary self-synchronizing rectifiers that can be used alone or in combination with other disclosed elements in various exemplary embodiments.

[0113] Figure 10 shows a more detailed schematic depiction of a V / I tuner based on Figure 6, according to an example of a power signal used to adjust to a transmitter resonator.

[0114] Figure 11 shows a flowchart of one of the near-field resonant wireless methods for transmitting power in a dual mode at a resonant power signal oscillation frequency according to an exemplary embodiment.

[0115] Figure 12 is a schematic representation of a multi-transmitter near-field resonant wireless power transmission system used to transmit power to a single receiver subsystem.

[0116] Figures 13A and 13B depict a multi-transmitter near-field resonant wireless power transmission system, one of the methods used to transmit power to a single receiver subsystem.

[0117] Figure 14 depicts a multi-transmitter near-field resonant wireless power transmission system, one of the systems used to transmit power to more than one receiver subsystem.

[0118] Figure 15 shows a flowchart of one of the wireless near-field methods for transmitting power from a multi-transmitter subsystem to a single-resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0119] Figure 16 shows a flowchart of another wireless near-field method for transmitting power from a multi-transmitter subsystem to a single-resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0120] Figure 17 shows a flowchart of one of the wireless near-field methods for transmitting power from a multi-transmitter subsystem to more than one resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0121] Figure 18 shows a flowchart of another wireless near-field method for transmitting power from a multi-transmitter subsystem to more than one resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0122] Figure 19A shows a near-field resonant wireless power transmission system for wirelessly transmitting power from a photovoltaic solar cell to an electrical load.

[0123] Figure 19B shows a power transmission system used to transmit electricity from a photovoltaic solar cell to an electrical load.

[0124] Figures 20A and 20B show the front and rear views of a solar cell array configured for use in a multi-pair configuration with the near-field resonant wireless power transmission system of Figure 19A.

[0125] Figures 21A and 21B show the front and rear views of a solar cell array configured for use in a one-to-one configuration with the near-field resonant wireless power transmission system of Figure 19A.

[0126] Figures 22A and 22B show the front and rear views of a solar cell array configured for use in a column-based configuration with the near-field resonant wireless power transmission system of Figure 19A.

[0127] Figure 23 shows a flowchart of a method for wirelessly transmitting power from a photovoltaic solar cell to an electrical load.

[0128] Figure 24 shows a flowchart of another method for wirelessly transmitting power from a photovoltaic solar cell array to an electrical load.

[0129] Figure 25 shows a flowchart of another method for wirelessly transmitting power from a photovoltaic solar cell array to an electrical load.

[0130] Figure 26 shows a flowchart of another method for wirelessly transmitting power from a photovoltaic solar cell array to an electrical load.

[0131] Figure 27A shows a portion of an electric vehicle using one embodiment of an electric transmission system.

[0132] Figure 27B shows another diagram of a portion of an electric vehicle using one embodiment of an electric transmission system.

[0133] Figure 28A shows a diagram of a computer monitor using one embodiment of a power transmission system.

[0134] Figure 28B shows a computer monitor using another embodiment of a power transmission system.

[0135] Figure 29 shows a flowchart of one method for transmitting power from a DC power source to an electrical load.

[0136] Figure 30 shows a flowchart of one of the further methods for transmitting power from a DC power source to an electrical load.

[0137] Figure 31 shows a flowchart of one method for transmitting power between a transmit and receive module in a dual-mode resonant near-field radio frequency power transmission system.

[0138] Figure 32 shows a schematic diagram of one of the bidirectional power transmission circuit devices.

[0139] Figure 33 shows one implementation of a bidirectional power transmission circuit device.

[0140] Figure 34A shows one embodiment of a bidirectional power transmission circuit device implemented in a silicon wafer identical to that of a photovoltaic cell.

[0141] Figure 34B shows the device of Figure 34A combined with a resonator on one surface of a silicon wafer.

[0142] Figure 35A shows a near-field resonant wireless power transmission system for wirelessly transmitting power from a photovoltaic solar cell to an AC power load.

[0143] Figure 35B shows a power transmission system used to transmit electricity from a photovoltaic solar cell to an AC power load.

[0144] Figure 36 shows a schematic diagram of one of the bidirectional power transmission circuit devices.

Claims

1. A bidirectional power transmission system, comprising: A multi-terminal power switching device includes at least one DC terminal, at least one AC terminal, and at least one control terminal. The multi-terminal power switching device is adjustable between an amplification state and a rectification state, and is configured to: bidirectionally transmit a DC voltage and a DC current via the at least one DC terminal, and bidirectionally transmit a power signal having an amplitude, a frequency, and a phase via the at least one AC terminal; a controller configured to: establish an oscillation signal having the frequency and phase of the power signal at the at least one control terminal of the multi-terminal power switching device, and adjust the multi-terminal power switching device between the amplification state and the rectification state by adjusting the phase of the oscillation signal; and a phase, frequency, and duration cyclic adjustment circuit that is in wired data communication with the controller, and the phase, frequency, and duration cyclic adjustment circuit is in wired electrical communication with the multi-terminal power switching device via the at least one control terminal.

2. As in request item 1, a bidirectional power transmission system, wherein: The power signal has an action time cycle; the phase, frequency and action time cycle adjustment circuit includes an oscillator for generating the oscillation signal under the instruction from the controller; and the phase, frequency and action time cycle adjustment circuit is further configured to adjust the action time cycle of the power signal by adjusting one of the action time cycles of the oscillation signal.

3. The bidirectional power transmission system as claimed in claim 1 further includes: A tuning network that communicates with the controller via wired data and with the multi-terminal power switching device via the at least one AC terminal, wherein the tuning network is configured to adjust the power signal to a tuned power signal upon instruction from the controller.

4. The bidirectional power transmission system as described in claim 3 further includes: An amplitude / frequency / phase detector is wired to the controller via data communication and wired to the tuning network via electrical communication, wherein the amplitude / frequency / phase detector is configured to determine an amplitude, a frequency, and a phase of any electrical signal transmitted between the tuning network and an AC load / source outside the bidirectional power transmission system.

5. As in claim 4, a bidirectional power transmission system, wherein, The phase, frequency, and duration adjustment circuit is configured to adjust the oscillation signal based on measurement data received directly from the amplitude / frequency / phase detector or through the controller.

6. As in request item 4, a bidirectional power transmission system, wherein, The tuning network includes a voltage-current tuner for adjusting a phase difference between a voltage and a current of the tuned power signal based on measurement data from the amplitude / frequency / phase detector when the multi-terminal power switching device is in the amplified state.

7. The bidirectional power transmission system as claimed in claim 4 further includes: A power management circuit is wired to the controller and wired to a DC power source / load outside the multi-terminal power switch and the bidirectional power transmission system. The power management circuit is configured to impedance match the multi-terminal power switch and the external DC power source / load and to adjust the DC power transmitted between the multi-terminal power switch and the DC power source / load based on measurement data received directly from the amplitude / frequency / phase detector or through the controller.

8. The bidirectional power transmission system as claimed in claim 7, further comprising: A voltage / current sensor, which communicates with the controller via wired data, is configured to determine a DC voltage and DC current transmitted between the multi-terminal power switching device and the power management circuit.

9. As in claim 8, a bidirectional power transmission system, wherein, The phase, frequency, and duration adjustment circuit is configured to adjust the oscillation signal based on one of the feedback signals received directly from the voltage / current sensor or through the controller.

10. The bidirectional power transmission system of claim 8 further includes: A memory is wired to communicate with the controller, the amplitude / frequency / phase detector, and the voltage / current detector, wherein the memory is configured to receive and store data received from the two detectors and to provide data communication from the two detectors to the controller.

11. As in claim 4, a bidirectional power transmission system, wherein, The tuning network further includes one or more of a compensation network, a matching network, and a filter.

12. The bidirectional power transmission system as claimed in claim 3 further includes: A modulator configured to modulate information onto at least one of the power signal and the DC voltage.

13. The bidirectional power transmission system as described in claim 12, wherein, The modulator includes at least one of the multi-terminal power switching device and the tuning network.

14. As in claim 4, a bidirectional power transmission system, wherein, The AC load / source outside the bidirectional power transmission system includes a transmitter-receiver resonator configured to: resonate at the frequency of the power signal; and transmit power in a bimodal manner.

15. The bidirectional power transmission system as described in claim 1, wherein, The bidirectional power transmission system is configured to modulate at least one of digital information and analog information onto at least one of the DC voltage, the power signal, and a harmonic of the power signal.

16. As in claim 1, a bidirectional power transmission system, wherein, All circuit components of the system are monolithically integrated into a single silicon single crystal wafer.

17. The bidirectional power transmission system as described in claim 1, wherein, At least a portion of the circuit elements of the system are integrated using microelectronic chip technology.

18. As in claim 3, a bidirectional power transmission system, wherein, The AC load / source includes a facility AC power grid.

19. As in claim 1, a bidirectional power transmission system, wherein, The multi-terminal power switching device includes a differential switch-mode self-synchronizing power amplifier / rectifier.

20. A bidirectional power transmission system, comprising: A multi-terminal power switching device includes at least one DC terminal, at least one AC terminal, and at least one control terminal. The multi-terminal power switching device is adjustable between an amplification state and a rectification state, and is configured to: bidirectionally transmit a DC voltage and a DC current via the at least one DC terminal, and bidirectionally transmit a power signal having an amplitude, a frequency, and a phase via the at least one AC terminal; a controller is configured to: establish an oscillation signal having the frequency and phase of the power signal at the at least one control terminal of the multi-terminal power switching device, and adjust the multi-terminal power switching device between the amplification state and the rectification state by adjusting the phase of the oscillation signal. An amplitude / frequency / phase detector is configured to determine an amplitude, a frequency, and a phase of any power signal transmitted between the multi-terminal power switch and an AC power grid of an external facility of the bidirectional power transmission system; and a phase, frequency, and duration cyclic adjustment circuit is configured to communicate with the controller via wired data and with the multi-terminal power switch via the at least one control terminal.

21. A monolithic integrated power device comprising at least one photovoltaic cell electrically communicating with a bidirectional power transmission circuit on a silicon single crystal wafer, the bidirectional power transmission circuit including a plurality of terminals disposed for electrically communicating with devices external to the power transmission circuit, the power transmission circuit comprising: A multi-terminal power switching device includes at least one DC terminal, at least one AC terminal, and at least one control terminal. The multi-terminal power switching device is adjustable between an amplification state and a rectification state, and is configured to: bidirectionally transmit a DC voltage and a DC current via the at least one DC terminal, and bidirectionally transmit a radio frequency power signal having an amplitude, a frequency, and a phase via the at least one AC terminal; and a phase, frequency, and duration cyclic adjustment circuit, which communicates wiredly with a controller and wiredly with the multi-terminal power switching device via the at least one control terminal. The phase, frequency, and duration cyclic adjustment circuit is configured to: establish a radio frequency oscillation signal having the frequency and phase of the radio frequency power signal at the at least one control terminal of the multi-terminal power switching device, and adjust the phase of the radio frequency oscillation signal under the command of the controller to adjust the multi-terminal power switching device between the amplification state and the rectification state.

22. A dual-mode near-field resonant wireless radio frequency power transfer system, configured to simultaneously perform capacitive power transfer and inductive power transfer at a variable resonant power signal oscillation frequency based on an adjustable transmission mode ratio of capacitive power transfer to inductive power transfer, the system comprising: A transmitter subsystem includes a transmitter antenna and a power signal tuner module, wherein the power signal tuner module adjusts the adjustable transmission mode ratio by adjusting a power signal supplied to the transmitter antenna subsystem via the power signal tuner module; and a receiver subsystem includes a receiver antenna subsystem for receiving power from the transmitter antenna according to the adjustable transmission mode ratio.

23. A dual-mode resonant near-field radio frequency power delivery system comprising a plurality of power transmission-receiver modules for simultaneously performing capacitive and inductive power delivery via a power signal at a power signal frequency according to an adjustable transmission mode ratio, wherein each of the plurality of power transmission-receiver modules is wiredly communicated with a transmitter-receiver resonator to exchange power with at least another power transmission-receiver module of the plurality of power transmission-receiver modules.

24. A near-field radio frequency method for transmitting power via a power signal at a power signal frequency, the method comprising: A dual-mode resonant near-field radio frequency power delivery system is provided, comprising one of a plurality of power transmission-receive modules, wherein each of the plurality of power transmission-receive modules communicates with a transmitter-receiver resonator via a wired connection to exchange power with at least one other power transmission-receive module; and the power delivery system is operated to simultaneously perform capacitive power delivery and inductive power delivery according to an adjustable transmission mode ratio.

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