Apparatus for estimating performance of MIMO system on basis of performance of SISO system, and method using same

Abstract

An apparatus for estimating the performance of a MIMO system, according to one embodiment of the present invention, comprises: an input processing unit for generating input information including SISO requirement performance, channel condition information, and cross-channel discrimination information; a MIMO requirement performance estimating unit using the channel condition information and the cross-channel discrimination information so as to generate multiple input multiple output (MIMO) requirement performance; and an output interface unit for generating a system output on the basis of the MIMO requirement performance.

Description

Device for estimating the performance of a MIMO system based on the performance of a SISO system and a method using the same

[0001] The present invention relates to a performance estimation technique for a broadcast signal transmission / reception system, and in particular to a performance estimation technique for a MIMO (Multi Input Multi Output) system.

[0002] Recently, technologies and standards for next-generation terrestrial broadcasting systems have been introduced to meet the demand for ultra-high-definition broadcasting services, ensure the efficient use of frequency resources, and combine services requiring different coverage areas and reception environments. However, improvements in the transmission rate of terrestrial broadcasting systems remain necessary due to the growing demand for higher resolutions, ultra-realistic media such as Augmented Reality (AR) and Virtual Reality (VR), and supplementary data for user experience, as well as the shortage of idle frequency resources resulting from the simultaneous provision of existing broadcasting services.

[0003] Modern terrestrial digital broadcasting standards such as ATSC 3.0 sought to overcome the transmission capacity limitations of a single broadcast frequency by applying multiple antenna technologies such as MIMO (Multiple Input Multiple Output), and adopted Layered Division Multiplexing technology in addition to TDM (Time Division Multiplexing) or FDM (Frequency Division Multiplexing) to support multiple services simultaneously.

[0004] MIMO used in ATSC 3.0 is a technology that increases transmission capacity by utilizing orthogonal polarization antennas to transmit two data streams over a single RF (Radio Frequency) channel. In this case, orthogonal polarization antennas consist of two antennas with polarizations orthogonal to each other, and the environment considers one where both vertically polarized and horizontally polarized antennas are installed at the transmitter and receiver. This type of MIMO is called 2x2 cross-polarized MIMO. In this case, each polarized antenna can be referred to as Antenna #1 (ANT 1) and Antenna #2 (ANT 2). Antenna #1 may be a vertically polarized antenna and Antenna #2 may be a horizontally polarized antenna, or conversely, Antenna #1 may be a horizontally polarized antenna and Antenna #2 may be a vertically polarized antenna.

[0005] Although layered division multiplexing is somewhat more complex than TDM and FDM, it offers a high level of flexibility and improved system performance.

[0006] Layered Division Multiplexing refers to a system that combines multiple layers into one for transmission. In its simplest form, considering a system with two layers—a core layer and an enhanced layer—the core layer generally refers to a layer with higher reception robustness compared to the enhanced layer. In the ATSC 3.0 standard, the transmission power allocated to the core layer is significantly greater than that allocated to the enhanced layer, thereby inducing priority decoding of the core layer at the receiver.

[0007] The power ratio of the enhanced layer relative to the core layer is called the injection level, and injection level information is transmitted to the receiver via L1 signaling.

[0008] Korean Published Patent No. 10-2018-0132525 proposes a structure for combining MIMO technology and layered division multiplexing technology for broadcast signal transmission / reception. In particular, Korean Published Patent No. 10-2018-0132525 discloses two types of structures: one in which MIMO is applied to both the core layer and the enhanced layer, and another in which MIMO is applied to only one of the core layer or the enhanced layer.

[0009] When MIMO is applied to a broadcast signal transmission / reception system, the receiver must be equipped with two antennas (a vertically polarized antenna and a horizontally polarized antenna) to fully recover the transmitted MIMO signal, and existing single-antenna receivers cannot receive signals transmitted via the MIMO method. In other words, because MIMO separates a single service into two different streams and transmits each separated stream to a respective antenna, a single-antenna receiver cannot recover the original service.

[0010] Therefore, when configuring LDM multiplexing including MIMO transmission signals, compatibility with existing single-antenna receivers must be considered.

[0011] If there is no need to guarantee compatibility with existing single-antenna receivers, when LDM technology and MIMO technology are applied together, the MIMO method can be applied to the core layer and the MIMO method can be applied to the enhanced layer.

[0012] However, when using LDM and MIMO technologies together while ensuring compatibility with existing single-antenna receivers, the core layer may apply the SISO (Single Input Single Output) method, and the enhanced layer may apply the MIMO method. In this case, SISO may not separate a service into multiple streams and transmit them independently. In this case, even if two antennas apply the same signal, it may be considered as SISO.

[0013] The ATSC 3.0 standard document A / 327 describes the Carrier-to-Noise Ratio (CNR) measurement for the modulation constellation-channel coding (ModCod) combination for single-layer SISO (Single Input Single Output) transmission, for network design and operation by network operators.

[0014] However, the required CNR threshold for ATSC 3.0 transmission systems with MIMO applied is unknown.

[0015] The objective of the present invention is to efficiently and accurately estimate the performance of a MIMO system from the performance of a SISO system using cross-channel discrimination such as cross-polarization discrimination (XPD).

[0016] In addition, the objective of the present invention is to efficiently and accurately estimate the performance of a layered MIMO system, in which layered division multiplexing and MIMO are applied together, as well as a general MIMO system, from the performance of a SISO system layer by layer.

[0017] In addition, the objective of the present invention is to efficiently and accurately estimate MIMO system performance from SISO system performance based on channel condition information.

[0018] In addition, the objective of the present invention is to efficiently and accurately estimate MIMO system performance from SISO system performance by simultaneously considering the effect of pilot boosting on channel estimation quality and the effect on the reduction of data signal power.

[0019] In addition, the objective of the present invention is to efficiently and accurately estimate the coverage of a MIMO system by estimating the performance of a MIMO system from the performance of a SISO system using cross-channel discrimination such as cross-polarization discrimination (XPD), channel condition information, and pilot boosting information.

[0020] An apparatus for estimating the performance of a MIMO system according to the present invention for achieving the above-mentioned purpose comprises: an input processing unit that generates input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information; a MIMO required performance estimation unit that generates MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the channel condition information and cross-channel discrimination information; and an output interface unit that generates a system output based on the MIMO required performance.

[0021] At this time, the MIMO required performance can be generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the channel condition information and the cross-channel distinction information.

[0022] At this time, the correction input value is input into a correction offset function, and the output of the correction offset function can correspond to the MIMO required performance.

[0023] At this time, the correction offset function may vary depending on the channel condition information.

[0024] At this time, the correction offset function may vary depending on the cross-channel distinction information.

[0025] At this time, the MIMO system is a first-type layered MIMO system, and the MIMO required performance may include one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer.

[0026] At this time, the core layer MIMO required performance and the enhanced layer MIMO required performance can be generated based on the injection level.

[0027] At this time, the MIMO required performance can be estimated using either a first mode corresponding to error-free complete channel estimation or a second mode corresponding to error-prone channel estimation.

[0028] At this time, the input information may further include pilot boosting information and pilot separation information in the second mode.

[0029] In addition, a method for estimating the performance of a MIMO system according to an embodiment of the present invention comprises: a step of generating input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information; a step of generating MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the channel condition information and cross-channel discrimination information; and a step of generating a system output based on the MIMO required performance.

[0030] At this time, the MIMO required performance can be generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the channel condition information and the cross-channel distinction information.

[0031] At this time, the correction input value is input into a correction offset function, and the output of the correction offset function can correspond to the MIMO required performance.

[0032] At this time, the correction offset function may vary depending on the channel condition information.

[0033] At this time, the correction offset function may vary depending on the cross-channel distinction information.

[0034] At this time, the MIMO system is a first type layered MIMO system, and the MIMO required performance may include one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer.

[0035] At this time, the core layer MIMO required performance and the enhanced layer MIMO required performance can be generated based on the injection level.

[0036] At this time, the MIMO required performance can be estimated using either a first mode corresponding to error-free complete channel estimation or a second mode corresponding to error-prone channel estimation.

[0037] At this time, the input information may further include pilot boosting information and pilot separation information in the second mode.

[0038] In addition, a method for estimating coverage of a MIMO system according to an embodiment of the present invention comprises: a step of generating input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information; a step of generating MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the channel condition information and cross-channel discrimination information; and a step of generating a coverage output based on the result of comparing the MIMO required performance with a comparison target performance corresponding to a specific location.

[0039] At this time, the MIMO required performance can be generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the channel condition information and the cross-channel distinction information.

[0040] According to the present invention, the performance of a MIMO system can be efficiently and accurately estimated from the performance of a SISO system by using cross-channel discrimination such as cross-polarization discrimination (XPD).

[0041] In addition, the present invention can efficiently and accurately estimate the performance of a layered MIMO system, in which layered division multiplexing and MIMO are applied together, as well as a general MIMO system, from the performance of a SISO system layer by layer.

[0042] In addition, the present invention can efficiently and accurately estimate MIMO system performance from SISO system performance based on channel condition information.

[0043] In addition, the present invention can efficiently and accurately estimate MIMO system performance from SISO system performance by simultaneously considering the effect of pilot boosting on channel estimation quality and the effect on the reduction of data signal power.

[0044] In addition, the present invention can efficiently and accurately estimate the coverage of a MIMO system by estimating the performance of a MIMO system from the performance of a SISO system using cross-channel discrimination such as cross-polarization discrimination (XPD), channel condition information, and pilot boosting information.

[0045] FIG. 1 is a block diagram showing an example of a broadcast signal transmission device according to an embodiment of the present invention.

[0046] FIG. 2 is a block diagram showing an example of a broadcast signal transmission device corresponding to a first type layered MIMO according to an embodiment of the present invention.

[0047] FIG. 3 is a block diagram showing an example of a broadcast signal transmission device corresponding to a second type layered MIMO according to an embodiment of the present invention.

[0048] FIG. 4 is a block diagram showing an example of an LDM coupling part illustrated in FIG. 2.

[0049] Figure 5 is a block diagram showing an example of an LDM coupling part illustrated in Figure 3.

[0050] Figure 6 is a diagram showing an example of a SISO distributed pilot pattern corresponding to SP3_2.

[0051] Figure 7 is a diagram showing an example of a Walsh-Hadamard encoded MIMO distributed pilot pattern corresponding to MP3_2.

[0052] Figure 8 is a diagram showing an example of a null-pilot encoded MIMO distributed pilot pattern corresponding to MP3_2.

[0053] Figure 9 is a diagram showing an example of a transmission signal configuration in the case where a SISO signal is transmitted through only one of two MIMO antennas.

[0054] Figure 10 is a diagram showing an example of a transmission signal configuration in the case where a SISO signal is transmitted through both MIMO antennas.

[0055] Figure 11 is a diagram comparing the SISO distributed pilot pattern and the MIMO distributed pilot pattern.

[0056] FIG. 12 is a block diagram showing an example of a broadcast signal transmission device using multiple transmission antennas and hierarchical division multiplexing.

[0057] FIG. 13 is a diagram showing a physical layer frame of a broadcast signal according to an embodiment of the present invention.

[0058] FIG. 14 is a diagram showing broadcast signal frames transmitted to two MIMO antennas according to an embodiment of the present invention.

[0059] FIG. 15 is a diagram showing an example in which, in a SISO subframe section, the SISO signal is transmitted only at the first polarization and the second polarization is disabled in that section.

[0060] FIG. 16 is a diagram showing an example in which a SISO signal is transmitted through both the first polarization and the second polarization in the SISO subframe section.

[0061] Figures 17 and 18 are diagrams showing examples of broadcast signal frames transmitted through two polarizations when layered MIMO is applied.

[0062] FIG. 19 is a diagram showing an example in which two or more of the subframes using SISO, MIMO, and layered MIMO methods are TDMed.

[0063] FIG. 20 is a diagram showing an example of a broadcast signal frame containing a second type layered MIMO subframe transmitted with two polarizations.

[0064] FIG. 21 is a diagram showing an example of a broadcast signal frame containing a first type layered MIMO subframe transmitted with two polarizations.

[0065] FIG. 22 is an operation flowchart illustrating a broadcast signal transmission method according to an embodiment of the present invention.

[0066] FIG. 23 is an operation flowchart illustrating a method for receiving a broadcast signal according to an embodiment of the present invention.

[0067] FIG. 24 is a block diagram showing the configuration of a computer system according to an embodiment of the present invention.

[0068] FIG. 25 is a block diagram showing an example of a device for estimating the performance of a MIMO system according to an embodiment of the present invention.

[0069] FIG. 26 is a block diagram showing an example of a device for estimating channel XPD from antenna XPD according to an embodiment of the present invention.

[0070] FIG. 27 is an operation flowchart illustrating an example of a method for estimating the performance of a MIMO system according to an embodiment of the present invention.

[0071] FIG. 28 is an operation flowchart illustrating an example of a method for estimating the coverage of a MIMO system according to an embodiment of the present invention.

[0072] The present invention will be described in detail below with reference to the accompanying drawings. Hereinafter, repetitive descriptions and detailed descriptions of known functions and configurations that may unnecessarily obscure the essence of the invention are omitted. Embodiments of the present invention are provided to more completely explain the invention to those with average knowledge in the art. Accordingly, the shapes and sizes of elements in the drawings may be exaggerated for clearer explanation.

[0073] Hereinafter, preferred embodiments according to the present invention will be described in detail with reference to the attached drawings.

[0074] When configuring LDM multiplexing including MIMO transmission signals, if compatibility with existing single-antenna receivers is considered, the SISO method can be applied to the core layer and MIMO can be applied only to the enhanced layer. Additionally, if compatibility with existing single-antenna receivers is not considered, the MIMO method can be applied to both the core layer and the enhanced layer.

[0075] At this time, the type (operation type) of the layered MIMO may be either a first type layered MIMO in which the MIMO is applied to both the core layer and the enhanced layer, or a second type layered MIMO in which the MIMO is applied only to the enhanced layer.

[0076] In particular, in the case of Type 2 layered MIMO, the SISO signal (LEGACY SERVICE) of the core layer may be transmitted through only one of the two MIMO antennas (VERTICAL, HORIZONTAL) (VERTICAL), and the other MIMO antenna (HORIZONTAL) may not transmit the core layer signal. Additionally, in the case of Type 2 layered MIMO, the two MIMO antennas (VERTICAL, HORIZONTAL) may transmit the same SISO signal (LEGACY SERVICE) of the core layer in the core layer, and each transmit two MIMO signals (STREAM 1, STREAM 2) in the enhanced layer.

[0077] In other words, the SISO signal transmitted to the core layer may be transmitted through only one antenna, or the SISO signal transmitted to the core layer may be transmitted through both antennas.

[0078] In cases where LDM and MIMO technologies are used together in a combined form of SISO and MIMO, backward compatibility with existing SISO receivers must be guaranteed, so L1 signaling must be applicable to both SISO receivers and MIMO receivers. Therefore, from the perspective of existing SISO receivers, L1 signaling fields must be transmitted in the same way as in the existing SISO method transmission to ensure normal operation of the SISO receiver.

[0079] FIG. 1 is a block diagram showing an example of a broadcast signal transmission device according to an embodiment of the present invention.

[0080] Referring to FIG. 1, a broadcast signal transmission device according to one embodiment of the present invention includes input formatting units (111, 121), BICM (Bit-Interleaver Coded Modulation) units (112, 122), a MIMO precoder (120), an LDM coupling unit (130), and a transmission signal generation unit (140).

[0081] A combination of Layered Division Multiplexing (LDM) and Multiple-Input Multiple-Output (MIMO) can be called Layered MIMO, which increases spectral efficiency by integrating two different multiplexing gains from independent domains. In this case, the two different multiplexing gains are the LDM gain from spectral reuse and the MIMO gain from spatial multiplexing. Layered MIMO is an extension of MIMO technology and may be a multiplexing technique specialized for multiple physical layer pipes containing one or more MIMO physical layer pipes.

[0082] In this case, the layered MIMO system may be limited to a 2-layer LDM having a MIMO-encoded enhanced layer. In this case, SISO or MIMO may be applied to the core layer. Ultimately, depending on the form of the core layer, two types of layered MIMO can be defined.

[0083] That is, a first type of layered MIMO in which the core layer and the enhanced layer physical layer pipes all use MIMO, and a second type of layered MIMO in which the core layer physical layer pipe(s) use SISO and the enhanced layer physical layer pipe(s) use MIMO can be defined.

[0084] In this case, MIMO processing in Layered MIMO may use a 2x2 cross-polarized antenna system. There may be at least two effective antenna units at the transmitter location, and the receiver's antenna requirements may vary depending on the signals intended to be received. If a service transmitted by a MIMO Physical Layer Pipe (PLP) is to be received, the receiver may include a cross-polar pair of antennas or more. If a service transmitted by Single-Input Single-Output (SISO) is to be received, the receiver may operate with a single antenna or a diversity antenna set.

[0085] At this time, a receiver capable of decoding MIMO PLP can also support SISO decoding.

[0086] In this case, when Type 2 layered MIMO is applied, compatibility with MIMO operation can determine the receiver's ability to decode each signal layer.

[0087] The input formatting unit (111) generates packetized data (baseband packets) in units of processing blocks of the transmitting system. At this time, the transmitting system can classify packets to which the same BICM (Bit Interleaved Coded Modulation) and transmission signal generation parameters are applied and define them as the same PLP (Physical Layer Pipe).

[0088] The BICM unit (112) can generate at least one core layer signal. At this time, the BICM unit (112) may include a Forward Error Correction (FEC) unit, a Bit Interleaver (BIL) unit, and a symbol mapping unit. At this time, the FEC unit may apply channel coding to baseband packets to generate bit groups, such as FEC frames (FEC packets). At this time, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. At this time, the BIL unit may perform bit interleaving on the FEC frames output from the FEC unit. At this time, the symbol mapping unit may generate data cells for transmitting output to be transmitted through an antenna for the output bit sequence of the BIL unit and output them as a core layer signal.

[0089] According to an embodiment, the BICM unit (112) may generate core layer MIMO (Multiple Input Multiple Output) signals. In this case, the BICM unit (112) may include a Forward Error Correction (FEC) unit, a Bit Interleaver (BIL) unit, and a Multi-Input Multi-Output (MIMO) MAP (mapping) unit. In this case, the FEC unit may apply channel coding to baseband packets to generate FEC frames (FEC packets), which are groups of bits. In this case, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. In this case, the BIL unit may perform bit interleaving on the FEC frames output from the FEC unit. In this case, the MIMO MAP unit may generate data cells for transmitting output to each of the multiple antennas for the output bit sequence of the BIL unit. To this end, the MIMO MAP section may be composed of two detailed blocks: a demultiplexer section and a bit-to-IQ mapping section. In this case, the demultiplexer section may group input bit sequences according to the modulation order and the number of multiple antennas to convert them into data cells. In this case, the bit sequences corresponding to each group may vary depending on the modulation order and the number of multiple antennas. The bit-to-IQ mapping section maps the output of the demultiplexer section to constellations corresponding to groups of bits corresponding to each antenna output, and generates data cells corresponding to each antenna output. In one embodiment, in a bit group, even-numbered bits may be mapped to data cells for the first antenna (first polarization), and odd-numbered bits may be mapped to data cells for the second antenna (second polarization).At this time, grouping of each bit in the MIMO MAP section or constellation mapping of bits using the same can also be performed using various methods not exemplified. At this time, the first polarization may be vertical polarization, and the second polarization may be horizontal polarization.

[0090] In this case, polarization can be the orientation of the electric field vector of a radiated electromagnetic wave with respect to the horizon as seen from the antenna. That is, polarization can describe the orientation of the wave emitted from which. This orientation can be planar or circular.

[0091] In the following, the first antenna may be replaced with the first polarization, and the second antenna may be replaced with the second polarization.

[0092] In the example illustrated in FIG. 1, the input formatting unit (111) and the BICM unit (112) may correspond to a core layer signal generating unit that generates at least one core layer signal corresponding to a core layer. In particular, when at least one core layer signal is a core layer MIMO signal, a part related to the core layer of the input formatting unit (111), the BICM unit (112), and the MIMO precoder (120) may correspond to a core layer generating unit.

[0093] The input formatting unit (121) generates packetized data (baseband packets) in units of processing blocks of the transmitting system. At this time, the transmitting system can classify packets to which the same BICM (Bit Interleaved Coded Modulation) and transmission signal generation parameters are applied and define them as the same PLP (Physical Layer Pipe).

[0094] The BICM section (122) may include a Forward Error Correction (FEC) section, a Bit Interleaver (BIL) section, and a Multi-Input Multi-Output (MIMO) MAP (mapping) section. In this case, the FEC section may apply channel coding to baseband packets to generate bit groups, such as FEC frames (FEC packets). In this case, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. In this case, the BIL section may perform bit interleaving on the FEC frames output from the FEC section. In this case, the MIMO MAP section may generate data cells for transmitting output to each of the multiple antennas for the output bit sequence of the BIL section. To this end, the MIMO MAP section may be composed of two detailed blocks: a DeMultiplexer section and a Bit to IQ mapping section. At this time, the demultiplexer unit may group the input bit sequence according to the modulation order and the number of multiple antennas to convert the input bit sequence into a data cell. At this time, the bit sequence corresponding to each group may differ depending on the modulation order and the number of multiple antennas. The bit-to-IQ mapping unit maps the output of the demultiplexer unit to constellations corresponding to groups of bits corresponding to each antenna output, and generates data cells corresponding to each antenna output. In one embodiment, the even-numbered bits in the bit group may be mapped to a data cell for the first antenna (first polarization), and the odd-numbered bits may be mapped to a data cell for the second antenna (second polarization). At this time, the grouping of each bit in the MIMO MAP unit or the constellation mapping of bits utilizing it may also be performed using various methods not exemplified. At this time, the first polarization may be vertically polarized, and the second polarization may be horizontally polarized.

[0095] In the example illustrated in FIG. 1, the input formatting unit (121) and the BICM unit (122) may correspond to an enhanced layer MIMO signal generation unit that generates enhanced layer MIMO (Multiple Input Multiple Output) signals corresponding to the enhanced layer. In particular, when MIMO precoding is performed, the input formatting unit (121), the BICM unit (122), and a part of the MIMO precoder (120) associated with the enhanced layer may correspond to an enhanced layer MIMO signal generation unit.

[0096] The MIMO precoder (120) may be enabled or disabled. In particular, when Type 1 layered MIMO is applied, MIMO precoding may be applied to the core layer and enhanced layer physical layer pipes. When Type 2 layered MIMO is applied, MIMO precoding may be applied only to the enhanced layer physical layer pipe(s). To reduce the complexity of the receiver, when Type 1 layered MIMO is applied, it may be required to apply the same I / Q polarization interleaving and phase hopping parameters to the enhanced layer physical layer pipes as to the core layer physical layer pipes associated with them. This means that if the core layer physical layer pipes enable I / Q polarization, the associated enhanced layer physical layer pipes must also enable I / Q polarization. Of course, the opposite is true, and the same method may be applied to phase hopping.

[0097] At this time, the MIMO precoder (120) may include a streaming combiner, an IQ polarization interleaving unit, and a phase hopping unit. At this time, the streaming combiner can combine two data cells entering as input and output. At this time, the IQ polarization interleaving unit can exchange the quadrature components of two data cells entering as input and output. At this time, the phase hopping unit can change the phase of the data cells entering as input and output. At this time, all three sub-blocks may be activated and operating, all may be deactivated and operating, or only some blocks may be activated and operating. Additionally, depending on the channel coding rate and modulation order applied to the data cells entering as input to each sub-block, each sub-block may output different signals or output the same signal. The MIMO precoder (120) illustrated in FIG. 1 can output two data cells to be output through a first antenna (first polarization) and a second antenna (second polarization) for each of the core layer and the enhanced layer.

[0098] The LDM coupling unit (130) performs layered multiplexing corresponding to the core layer and the enhanced layer and outputs a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization.

[0099] When the BICM unit (112) outputs core layer MIMO signals, the first polarization signal may be generated by hierarchically dividing multiplexing one of the core layer MIMO signals and one of the enhanced layer MIMO signals, and the second polarization signal may be generated by hierarchically dividing multiplexing another of the core layer MIMO signals and another of the enhanced layer MIMO signals.

[0100] When the BICM unit (112) outputs a core layer signal corresponding to the SISO, the first polarization signal is generated by hierarchically dividing multiplexing one of the at least one core layer signal and one of the enhanced layer MIMO signals, and the other of the enhanced layer MIMO signals can be output as the second polarization signal.

[0101] The transmission signal generation unit (140) generates a first polarization transmission signal using the first polarization signal and generates a second polarization transmission signal using the second polarization signal.

[0102] The transmission signal generation unit (140) includes framing and interleaving units (141, 142) and waveform generators (145, 146).

[0103] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (141) on the first polarization signal output through the LDM coupling unit (130). The output of the framing & interleaving unit (141) is input to the waveform generator (145) and output to the first antenna as the first polarization transmission signal.

[0104] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (142) on the second polarization signal output through the LDM coupling unit (130). The output of the framing & interleaving unit (142) is input to the waveform generator (146) and output to the second antenna as a second polarization transmission signal.

[0105] The framing and interleaving units (141, 142) illustrated in FIG. 1 can each generate a signal corresponding to a frame to be transmitted through an antenna using data cells that are input. At this time, the framing and interleaving units (141, 142) may or may not perform time interleaving with the input data cells. At this time, the framing and interleaving units (141, 142) can perform framing by configuring a preamble symbol and a subframe with respect to the data cells. At this time, the preamble symbol may not include the data cells. At this time, frequency interleaving may or may not be applied with the activation.

[0106] At this time, at least one of the first polarization transmission signal and the second polarization transmission signal includes a preamble, and the preamble may include a plurality of signaling fields for identifying the type of layered MIMO.

[0107] At this time, the type of the layered MIMO may be either a first type layered MIMO in which MIMO is applied to both the core layer and the enhanced layer, or a second type layered MIMO in which MIMO is applied only to the enhanced layer.

[0108] At this time, if the type of the layered MIMO is the first type layered MIMO, the at least one core layer signal is a core layer MIMO (Multiple Input Multiple Output) signal, the first polarization signal is generated by hierarchically dividing multiplexing one of the core layer MIMO signals and one of the enhanced layer MIMO signals, and the second polarization signal can be generated by hierarchically dividing multiplexing another of the core layer MIMO signals and another of the enhanced layer MIMO signals.

[0109] At this time, if the type of the layered MIMO is the second type layered MIMO, the first polarization signal is generated by layering multiplexing at least one core layer signal and one of the enhanced layer MIMO signals, and the other of the enhanced layer MIMO signals can be output as the second polarization signal.

[0110] At this time, the plurality of signaling fields may be a first 1-bit field that is set to 0 when the subframe includes a physical layer pipe to which MIMO processing is not applied, and a second 1-bit field that is set to 1 when LDM is applied to the subframe and MIMO is used only in the enhanced layer and not in the core layer.

[0111] At this time, the type of layered MIMO can be signaled by using the first 1-bit field and the second 1-bit field together (signaled by the second 1-bit field in conjunction with the first 1-bit field).

[0112] At this time, when layered division multiplexing is applied to a subframe, the first 1-bit field may be set to 1 and the second 1-bit field may be set to 0 to represent the first type layered MIMO, and the first 1-bit field may be set to 0 and the second 1-bit field may be set to 1 to represent the second type layered MIMO.

[0113] At this time, the setting of the second 1-bit field to 1 may be mutually exclusive with the setting of the first 1-bit field to 1.

[0114] At this time, the first type layered MIMO corresponds to all physical layer pipes within the subframe using MIMO, and the second type layered MIMO may correspond to at least one SISO physical layer pipe and at least one MIMO physical layer pipe existing together in the subframe.

[0115] According to an embodiment, the first polarization transmission signal and the second polarization transmission signal may each include a preamble, but only one of them may include a preamble.

[0116] When the first polarization transmission signal includes a first preamble and the second polarization transmission signal includes a second preamble, the first preamble and the second preamble may each include a 1-bit L1B_mimo_scattered_pilot_encoding field set to 0. Furthermore, the first preamble and the second preamble may include the same L1 signaling information.

[0117] If only one of the first polarization transmission signal and the second polarization transmission signal includes a preamble, this preamble may be applied not only to the polarization (antenna) transmitting the preamble but also to other polarizations (antennas). For example, if only the first polarization transmission signal includes a preamble, the signaling fields included in this preamble may be used by the second polarization as well as the first polarization.

[0118] The grouped data cells, which are the outputs of the framing and interleaving units (141, 142), are input to the waveform generators (145, 146). At this time, the waveform generators (145, 146) can each perform an Inverse Fast Fourier Transform (IFFT) through pilot insertion and insert a guard interval symbol. Additionally, the waveform generators (145, 146) can each generate a bootstrap symbol and output it by placing it at the very beginning of the transmission frame.

[0119] In particular, when a second type layered MIMO is applied, the waveform generator (146) may apply power scaling for the second polarization in the IFFT step according to an injection level corresponding to the second polarization (which may be the same as the injection level corresponding to the first polarization). At this time, the power of the second polarization transmission signal may be lower than the power of the first polarization transmission signal.

[0120] Information regarding distributed pilots inserted through waveform generators (145, 146) may be included in a preamble generated by framing and interleaving units (141, 142).

[0121] In the example illustrated in Fig. 1, the dotted arrows may indicate signal flows related only to the first type layered MIMO.

[0122] In FIG. 1 and other drawings, blocks indicated by dashed lines that do not include other blocks may be components that can be disabled.

[0123] FIG. 2 is a block diagram showing an example of a broadcast signal transmission device corresponding to a first type layered MIMO according to an embodiment of the present invention.

[0124] Figure 2 shows an example of a transmitter configuration in which a MIMO signal is transmitted through the core layer and also through the enhanced layer.

[0125] Referring to FIG. 2, a broadcast signal transmission device corresponding to a first type layered MIMO according to an embodiment of the present invention includes a core layer MIMO signal generation unit (210), an enhanced layer MIMO signal generation unit (220), an LDM coupling unit (230), and a transmission signal generation unit (240).

[0126] The core layer MIMO signal generation unit (210) generates core layer MIMO (Multiple Input Multiple Output) signals.

[0127] The core layer MIMO signal generation unit (210) includes an input formatting unit (211), a core layer BICM unit (212), and a MIMO precoder (213).

[0128] The input formatting unit (211) generates packetized data (baseband packets) in units of processing blocks of the transmitting system. At this time, the transmitting system can classify packets to which the same BICM (Bit Interleaved Coded Modulation) and transmission signal generation parameters are applied and define them as the same PLP (Physical Layer Pipe).

[0129] The core layer BICM section (212) may include a Forward Error Correction (FEC) section, a Bit Interleaver (BIL) section, and a Multi-Input Multi-Output (MIMO) MAP (mapping) section. In this case, the FEC section may apply channel coding to baseband packets to generate bit groups, such as FEC frames (FEC packets). In this case, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. In this case, the BIL section may perform bit interleaving on the FEC frames output from the FEC section. In this case, the MIMO MAP section may generate data cells for transmitting output to each of the multiple antennas for the output bit sequence of the BIL section. To this end, the MIMO MAP section may be composed of two detailed blocks: a DeMultiplexer section and a Bit to IQ mapping section. At this time, the demultiplexer unit may group the input bit sequence according to the modulation order and the number of multiple antennas to convert the input bit sequence into a data cell. At this time, the bit sequence corresponding to each group may differ depending on the modulation order and the number of multiple antennas. The bit-to-IQ mapping unit maps the output of the demultiplexer unit to constellations corresponding to groups of bits corresponding to each antenna output, and generates data cells corresponding to each antenna output. In one embodiment, the even-numbered bits in the bit group may be mapped to a data cell for the first antenna (first polarization), and the odd-numbered bits may be mapped to a data cell for the second antenna (second polarization). At this time, the grouping of each bit in the MIMO MAP unit or the constellation mapping of bits utilizing it may also be performed using various methods not exemplified. At this time, the first polarization may be vertically polarized, and the second polarization may be horizontally polarized.

[0130] In this case, polarization can be the orientation of the electric field vector of a radiated electromagnetic wave with respect to the horizon as seen from the antenna. That is, polarization can describe the orientation of the wave emitted from which. This orientation can be planar or circular.

[0131] In the following, the first antenna may be replaced with the first polarization, and the second antenna may be replaced with the second polarization.

[0132] Two groups of data cells are input into a MIMO precoder (213).

[0133] At this time, the MIMO precoder (213) may include a streaming combiner, an IQ polarization interleaving unit, and a phase hopping unit. At this time, the streaming combiner can combine two data cells entering as input and output. At this time, the IQ polarization interleaving unit can exchange the quadrature components of two data cells entering as input and output. At this time, the phase hopping unit can change the phase of the data cells entering as input and output. At this time, all three sub-blocks may be activated and operating, all may be deactivated and operating, or only some blocks may be activated and operating. Additionally, depending on the channel coding rate and modulation order applied to the data cells entering as input to each sub-block, each sub-block may output different signals or output the same signal. The MIMO precoder (213) illustrated in FIG. 2 can output two data cells to be output through a first antenna (first polarization) and a second antenna (second polarization).

[0134] The enhanced layer MIMO signal generation unit (220) generates enhanced layer MIMO (Multiple Input Multiple Output) signals.

[0135] The enhanced layer MIMO signal generation unit (220) includes an input formatting unit (221), an enhanced layer BICM unit (222), and a MIMO precoder (223).

[0136] The input formatting unit (221) generates packetized data (baseband packets) in units of processing blocks of the transmitting system. At this time, the transmitting system can classify packets to which the same BICM (Bit Interleaved Coded Modulation) and transmission signal generation parameters are applied and define them as the same PLP (Physical Layer Pipe).

[0137] The enhanced layer BICM section (222) may include a Forward Error Correction (FEC) section, a Bit Interleaver (BIL) section, and a Multi-Input Multi-Output (MIMO) MAP (mapping) section. In this case, the FEC section may apply channel coding to baseband packets to generate bit groups, such as FEC frames (FEC packets). In this case, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. In this case, the BIL section may perform bit interleaving on the FEC frames output from the FEC section. In this case, the MIMO MAP section may generate data cells for transmitting output to each of the multiple antennas for the output bit sequence of the BIL section. To this end, the MIMO MAP section may be composed of two detailed blocks: a DeMultiplexer section and a Bit to IQ mapping section. At this time, the demultiplexer unit may group the input bit sequence according to the modulation order and the number of multiple antennas to convert the input bit sequence into a data cell. At this time, the bit sequence corresponding to each group may differ depending on the modulation order and the number of multiple antennas. The bit-to-IQ mapping unit maps the output of the demultiplexer unit to constellations corresponding to groups of bits corresponding to each antenna output, and generates data cells corresponding to each antenna output. In one embodiment, the even-numbered bits in the bit group may be mapped to a data cell for the first antenna (first polarization), and the odd-numbered bits may be mapped to a data cell for the second antenna (second polarization). At this time, the grouping of each bit in the MIMO MAP unit or the constellation mapping of bits utilizing it may also be performed using various methods not exemplified. At this time, the first polarization may be vertically polarized, and the second polarization may be horizontally polarized.

[0138] Two groups of data cells are input into a MIMO precoder (223).

[0139] At this time, the MIMO precoder (223) may include a streaming combiner, an IQ polarization interleaving unit, and a phase hopping unit. At this time, the streaming combiner can combine two data cells entering as input and output. At this time, the IQ polarization interleaving unit can exchange the quadrature components of two data cells entering as input and output. At this time, the phase hopping unit can change the phase of the data cells entering as input and output. At this time, all three sub-blocks may be activated and operating, all may be deactivated and operating, or only some blocks may be activated and operating. Additionally, depending on the channel coding rate and modulation order applied to the data cells entering as input to each sub-block, each sub-block may output different signals or output the same signal. The MIMO precoder (223) illustrated in FIG. 2 can output two data cells to be output through a first antenna (first polarization) and a second antenna (second polarization).

[0140] The LDM coupling unit (230) performs layered multiplexing corresponding to the core layer and the enhanced layer and outputs a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization.

[0141] In the example of FIG. 2, the LDM coupling unit (230) hierarchically divides multiplexes one of the core layer MIMO signals and one of the enhanced layer MIMO signals to output a first polarization signal corresponding to the first polarization (first antenna), and hierarchically divides multiplexes another of the core layer MIMO signals and another of the enhanced layer MIMO signals to output a second polarization signal corresponding to the second polarization (second antenna).

[0142] The transmission signal generation unit (240) generates a first polarization transmission signal using the first polarization signal and generates a second polarization transmission signal using the second polarization signal.

[0143] The transmission signal generation unit (240) includes framing and interleaving units (241, 242) and waveform generators (245, 246).

[0144] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (241) on the first polarization signal output through the LDM coupling unit (230). The output of the framing & interleaving unit (241) is input to the waveform generator (245) and output to the first antenna as the first polarization transmission signal.

[0145] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (242) on the second polarization signal output through the LDM coupling unit (230). The output of the framing & interleaving unit (242) is input to the waveform generator (246) and output to the second antenna as a second polarization transmission signal.

[0146] The framing and interleaving units (241, 242) illustrated in FIG. 2 can each generate a signal corresponding to a frame to be transmitted through an antenna using data cells that are input. At this time, the framing and interleaving units (241, 242) may or may not perform time interleaving with the input data cells. At this time, the framing and interleaving units (241, 242) can perform framing by configuring a preamble symbol and a subframe with respect to the data cells. At this time, the preamble symbol may not include the data cells. At this time, frequency interleaving may or may not be applied with the activation.

[0147] According to an embodiment, the first polarization transmission signal and the second polarization transmission signal may each include a preamble, but only one of them may include a preamble.

[0148] The grouped data cells, which are the outputs of the framing and interleaving units (241, 242), are input to the waveform generators (245, 246). At this time, the waveform generators (245, 246) can each perform an Inverse Fast Fourier Transform (IFFT) through pilot insertion and insert a guard interval symbol. Additionally, the waveform generators (245, 246) can each generate a bootstrap symbol and output it by placing it at the very beginning of the transmission frame.

[0149] The broadcast signal transmitter illustrated in FIG. 2 may correspond to a simple combination between MIMO physical layer pipes. In this case, constellation superposition may be applied per polarization. That is, the constellation symbol of the core layer physical layer pipe associated with the first polarization may be superposed with the constellation symbol of the enhanced layer physical layer pipe associated with the first polarization. Similarly, the constellation symbol of the core layer physical layer pipe associated with the second polarization may be superposed with the constellation symbol of the enhanced layer physical layer pipe associated with the second polarization.

[0150] FIG. 3 is a block diagram showing an example of a broadcast signal transmission device corresponding to a second type layered MIMO according to an embodiment of the present invention.

[0151] Figure 3 shows an example of a transmitter configuration in which a SISO signal is transmitted through the core layer and a MIMO signal is transmitted through the enhanced layer.

[0152] Referring to FIG. 3, a broadcast signal transmission device corresponding to a second type layered MIMO according to an embodiment of the present invention includes a core layer signal generation unit (310), an enhanced layer MIMO signal generation unit (320), an LDM coupling unit (330), and a transmission signal generation unit (340).

[0153] The core layer signal generation unit (310) generates a core layer signal (SISO signal).

[0154] The core layer signal generation unit (310) includes an input formatting unit (311) and a core layer BICM (Bit-Interleaved Coded Modulation) unit (312).

[0155] The input formatting unit (311) generates packetized data (baseband packets) in units of processing blocks of the transmitting system. At this time, the transmitting system can classify packets to which the same BICM (Bit Interleaved Coded Modulation) and transmission signal generation parameters are applied and define them as the same PLP (Physical Layer Pipe).

[0156] The core layer BICM section (312) may include a Forward Error Correction (FEC) section, a Bit Interleaver (BIL) section, and a symbol mapping section. At this time, the FEC section may apply channel coding to baseband packets to generate bit groups, such as FEC frames (FEC packets). At this time, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. At this time, the BIL section may perform bit interleaving on the FEC frames output from the FEC section. At this time, the symbol mapping section may generate data cells for transmitting output to be transmitted through an antenna for the output bit sequence of the BIL section and output them as core layer signals.

[0157] The enhanced layer MIMO signal generation unit (320) generates enhanced layer MIMO (Multiple Input Multiple Output) signals.

[0158] The enhanced layer MIMO signal generation unit (320) includes an input formatting unit (321), an enhanced layer BICM unit (322), and a MIMO precoder (323).

[0159] The input formatting unit (321) generates packetized data (baseband packets) in units of processing blocks of the transmitting system. At this time, the transmitting system can classify packets to which the same BICM (Bit Interleaved Coded Modulation) and transmission signal generation parameters are applied and define them as the same PLP (Physical Layer Pipe).

[0160] The enhanced layer BICM section (322) may include a Forward Error Correction (FEC) section, a Bit Interleaver (BIL) section, and a Multi-Input Multi-Output (MIMO) MAP (mapping) section. In this case, the FEC section may apply channel coding to baseband packets to generate bit groups, such as FEC frames (FEC packets). In this case, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding. In this case, the BIL section may perform bit interleaving on the FEC frames output from the FEC section. In this case, the MIMO MAP section may generate data cells for transmitting output to each of the multiple antennas for the output bit sequence of the BIL section. To this end, the MIMO MAP section may be composed of two detailed blocks: a DeMultiplexer section and a Bit to IQ mapping section. At this time, the demultiplexer unit may group the input bit sequence according to the modulation order and the number of multiple antennas to convert the input bit sequence into a data cell. At this time, the bit sequence corresponding to each group may differ depending on the modulation order and the number of multiple antennas. The bit-to-IQ mapping unit maps the output of the demultiplexer unit to constellations corresponding to groups of bits corresponding to each antenna output, and generates data cells corresponding to each antenna output. In one embodiment, the even-numbered bits in the bit group may be mapped to a data cell for the first antenna (first polarization), and the odd-numbered bits may be mapped to a data cell for the second antenna (second polarization). At this time, the grouping of each bit in the MIMO MAP unit or the constellation mapping of bits utilizing it may also be performed using various methods not exemplified. At this time, the first polarization may be vertically polarized, and the second polarization may be horizontally polarized.

[0161] In this case, polarization can be the orientation of the electric field vector of a radiated electromagnetic wave with respect to the horizon as seen from the antenna. That is, polarization can describe the orientation of the wave emitted from which. This orientation can be planar or circular.

[0162] In the following, the first antenna may be replaced with the first polarization, and the second antenna may be replaced with the second polarization.

[0163] Two groups of data cells are input into a MIMO precoder (323).

[0164] At this time, the MIMO precoder (323) may include a streaming combiner, an IQ polarization interleaving unit, and a phase hopping unit. At this time, the streaming combiner can combine two data cells entering as input and output. At this time, the IQ polarization interleaving unit can exchange the quadrature components of two data cells entering as input and output. At this time, the phase hopping unit can change the phase of the data cells entering as input and output. At this time, all three sub-blocks may be activated and operating, all may be deactivated and operating, or only some blocks may be activated and operating. Additionally, depending on the channel coding rate and modulation order applied to the data cells entering as input to each sub-block, each sub-block may output different signals or output the same signal. The MIMO precoder (323) illustrated in FIG. 3 can output two data cells to be output through a first antenna (first polarization) and a second antenna (second polarization).

[0165] The LDM coupling unit (330) performs hierarchical division multiplexing on one of the core layer signal and the enhanced layer MIMO signals to output a first polarization signal corresponding to the first polarization (first antenna), and outputs the other of the enhanced layer MIMO signals as is as a second polarization signal corresponding to the second polarization (second antenna).

[0166] At this time, the LDM coupling unit (330) can output the second polarization signal with unity power.

[0167] The transmission signal generation unit (340) generates a first polarization transmission signal using the first polarization signal and generates a second polarization transmission signal using the second polarization signal.

[0168] The transmission signal generation unit (340) includes framing and interleaving units (341, 342) and waveform generators (345, 346).

[0169] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (341) on the first polarization signal output through the LDM coupling unit (330). The output of the framing & interleaving unit (341) is input to the waveform generator (345) and output to the first antenna as the first polarization transmission signal.

[0170] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (342) on the second polarization signal output through the LDM coupling unit (330). The output of the framing & interleaving unit (342) is input to the waveform generator (346) and output to the second antenna as a second polarization transmission signal.

[0171] The framing and interleaving units (341, 342) illustrated in FIG. 3 can each generate a signal corresponding to a frame to be transmitted through an antenna using data cells that are input. At this time, the framing and interleaving units (341, 342) may or may not perform time interleaving with the input data cells. At this time, the framing and interleaving units (341, 342) may perform framing by configuring a preamble symbol and a subframe with respect to each data cell. At this time, the preamble symbol may not include the data cell. At this time, frequency interleaving may or may not be applied with the activation.

[0172] According to an embodiment, the first polarization transmission signal and the second polarization transmission signal may each include a preamble, but only one of them may include a preamble.

[0173] When the first polarization transmission signal includes a first preamble and the second polarization transmission signal includes a second preamble, the first preamble and the second preamble may each include a 1-bit L1B_mimo_scattered_pilot_encoding field set to 0. Furthermore, the first preamble and the second preamble may include the same L1 signaling information.

[0174] If only one of the first polarization transmission signal and the second polarization transmission signal includes a preamble, this preamble may be applied not only to the polarization (antenna) transmitting the preamble but also to other polarizations (antennas). For example, if only the first polarization transmission signal includes a preamble, the signaling fields included in this preamble may be used by the second polarization as well as the first polarization.

[0175] The grouped data cells, which are the outputs of the framing and interleaving units (341, 342), are input to the waveform generators (345, 346). At this time, the waveform generators (345, 346) can each perform an Inverse Fast Fourier Transform (IFFT) through pilot insertion and insert a guard interval symbol. Additionally, the waveform generators (345, 346) can each generate a bootstrap symbol and output it by placing it at the very beginning of the transmission frame.

[0176] In particular, the waveform generator (346) may apply power scaling for the second polarization in the IFFT step according to an injection level corresponding to the second polarization (which may be the same as the injection level corresponding to the first polarization). At this time, the power of the second polarization transmission signal may be lower than the power of the first polarization transmission signal.

[0177] Information regarding distributed pilots inserted through waveform generators (345, 346) may be included in a preamble generated by framing and interleaving units (341, 342).

[0178] In the example illustrated in FIG. 3, the second type layered MIMO can multiplex SISO and MIMO physical layer pipes within a subframe. This multiplexing scheme allows a receiver compatible only with SISO to receive core layer physical layer pipe(s) without being affected by the presence of enhanced layer physical layer pipe(s) using MIMO.

[0179] In Type 2 layered MIMO, MIMO precoding can be applied exclusively to the enhanced layer physical layer pipe(s).

[0180] In this case, layered MIMO may be prohibited from being applied to Bootstrap or Preamble.

[0181] At this time, layered MIMO processing can be applied to subframes individually according to the first 1-bit field (L1D_mimo or L1B_first_sub_mimo), the second 1-bit field (L1D_mimo_mixed or L1B_first_sub_mimo_mixed), and L1D_plp_layer settings transmitted through the preamble of each frame.

[0182] FIG. 4 is a block diagram showing an example of the LDM coupling part (230) illustrated in FIG. 2.

[0183] Referring to FIG. 4, the LDM coupling unit (230) includes injection level controllers (231, 235), coupling units (232, 236), and power normalizers (233, 237).

[0184] The LDM coupling unit (230) performs layered multiplexing corresponding to the core layer and the enhanced layer and outputs a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization.

[0185] That is, the LDM coupling part (230) is the core layer MIMO signals (S C,1 , S C,2 One of ) (S C,1 ) and enhanced layer MIMO signals (S E,1 , S E,2 One of ) (S E,1 ) hierarchically divided multiplexed to obtain a first polarization signal (β(S) corresponding to the first polarization (POLARIZATION #1). C,1 + αS E,1 Outputs as )) and core layer MIMO signals (S C,1 , S C,2 The other one of ) (S C,2 ) and enhanced layer MIMO signals (S E,1 , S E,2 The other one of ) (S E,2 ) hierarchically divided multiplexed to obtain a second polarization signal (β(S) corresponding to the second polarization (POLARIZATION #2). C,2 + αS E,2 Outputs as ))

[0186] The injection level controller (231) uses enhanced layer MIMO signals (S) for layer division multiplexing. E,1 , S E,2 One of ) (S E,1 Adjusts the power of ).

[0187] The injection level controller (235) uses enhanced layer MIMO signals (S) for layer division multiplexing. E,1 , S E,2 The other one of ) (S E,2 Adjusts the power of ).

[0188] The combiner (232) combines core layer MIMO signals (S C,1 , S C,2 One of ) (S C,1 One of the enhanced layer signals (αS) whose power is regulated by the injection level controller (231) E,1 Combines ).

[0189] The combiner (236) combines core layer MIMO signals (S C,1 , S C,2 The other one of ) (S C,2 One of the enhanced layer signals (αS) whose power is regulated by the injection level controller (235) E,2 Combines ).

[0190] The power normalizer (233) performs power normalization of the transmitted power and outputs a first polarization signal.

[0191] The power normalizer (237) performs power normalization of the transmitted power and outputs a second polarization signal.

[0192] As such, the LDM coupling unit illustrated in FIG. 4 combines the core layer signal and the enhanced layer signal through layer division multiplexing for the first polarization and the second polarization. That is, in the structure illustrated in FIG. 4, constellation-superposed signals can be transmitted in the first and second polarizations.

[0193] The first type layered MIMO illustrated in FIG. 4 must combine core and enhanced layer physical layer pipes using MIMO. In this case, constellation superposition may be required to be applied to MIMO-precoded cells (whether the MIMO precoding function is enabled or disabled).

[0194] In the example illustrated in FIG. 4, the injection level controllers (231, 235) can use the same injection level.

[0195] FIG. 5 is a block diagram showing an example of the LDM coupling part (330) illustrated in FIG. 3.

[0196] Referring to FIG. 5, the LDM coupling unit (330) includes an injection level controller (410), a coupling unit (420), and a power normalizer (430).

[0197] The LDM coupling part (330) is a core layer signal (S C ) and enhanced layer MIMO signals (S E,1 , S E,2 One of ) (S E,1 ) hierarchically divided multiplexed to obtain a first polarization signal (β(S) corresponding to the first polarization (POLARIZATION #1). C + αS E,1 Outputs as )) and enhanced layer MIMO signals (S E,1 , S E,2 The other one of ) (S E,2 ) is output as is as a second polarization signal corresponding to the second polarization.

[0198] The injection level controller (410) uses enhanced layer MIMO signals (S) for layer division multiplexing. E,1 , S E,2 One of ) (S E,1 Adjusts the power of ).

[0199] The combiner (420) is a core layer signal (S COne of the enhanced layer signals (αS) whose power is regulated by the injection level controller (410) E,1 Combines ).

[0200] The power normalizer (430) performs power normalization of the transmitted power and outputs a first polarization signal.

[0201] As such, the LDM coupling unit illustrated in FIG. 5 combines the core layer signal and the enhanced layer signal through layer division multiplexing for the first polarization, but for the second polarization, the combination of the two layer signals through layer division multiplexing is not performed, and the input MIMO signal (S E,2 ) outputs as is. That is, in the structure illustrated in FIG. 5, constellation-superposed signals are transmitted only in POLARIZATION #1, and POLARIZATION #2 can transmit a dedicated MIMO stream consisting exclusively of enhanced layer cells.

[0202] At this time, in the first polarization, at least one SISO (Single Input Single Output) PLP (Physical Layer Pipe) and at least one MIMO PLP superposed with the at least one SISO PLP can share pilot cells. That is, the SISO PLP(s) and MIMO PLP(s) superposed by the broadcast signal transmitting device shown in FIGS. 3 and 5 can share pilot cells transmitted through the first polarization (first antenna). This can also be viewed as the pilot cells transmitted through the first polarization (first antenna) of the broadcast signal transmitting device shown in FIGS. 3 and 5 being shared by the core layer used for SISO transmission and the enhanced layer used for MIMO transmission.

[0203] At this time, the first polarization transmission signal and the second polarization transmission signal may be generated using only the first MIMO distributed pilot encoding among the first MIMO distributed pilot encoding that transmits pilots to the same OFDM cell positions for the first polarization and the second polarization, and the second MIMO distributed pilot encoding that transmits pilots to different OFDM cell positions for the first polarization and the second polarization.

[0204] At this time, the first MIMO distributed pilot encoding may correspond to a first group in which identical pilots are transmitted for the first polarization and the second polarization, and a second group in which pilots with opposite phases are transmitted for the first polarization and the second polarization.

[0205] At this time, the second MIMO distributed pilot encoding may correspond to a first group in which only the pilots for the first polarization are transmitted with valid power and the pilots for the second polarization are transmitted with null power, and a second group in which only the pilots for the second polarization are transmitted with valid power and the pilots for the first polarization are transmitted with null power.

[0206] At this time, the first MIMO distributed pilot encoding may be a Walsh-Hadamard encoding, and the second MIMO distributed pilot encoding may be a Null pilot encoding.

[0207] At this time, at least one of the first polarization transmission signal and the second polarization transmission signal may include a preamble. At this time, the preamble may include a 1-bit L1B_mimo_scattered_pilot_encoding field set to 0.

[0208] At this time, the 1-bit L1B_mimo_scattered_pilot_encoding field set to 0 can indicate both a MIMO pilot pattern with Walsh-Hadamard encoding and the SISO pilot pattern simultaneously.

[0209] In this way, when considering a conventional single-antenna receiver in a broadcast signal transmitter that uses both LDM and MIMO, a conflict may occur between the pilot pattern for the MIMO terminal and the pilot pattern for the SISO terminal (between the signaling information of the pilot pattern for the MIMO terminal and the signaling information of the pilot pattern for the SISO terminal).

[0210] In ATSC 3.0 broadcasting systems, L1B_first_sub_scattered_pilot_pattern (for the first subframe) and L1D_scattered_pilot_pattern (for other subframes) are used as scattered pilot pattern identification fields, and the scattered pilot pattern is signaled through these fields.

[0211] These fields are signaling fields commonly used for SISO transmission and MIMO transmission, and the receiver can determine the exact distributed pilot pattern by combining these fields with other MIMO-related fields (e.g., L1B_first_sub_mimo (for the first subframe) and L1D_mimo (for other subframes)) to distinguish whether it is a SISO distributed pilot pattern or a MIMO distributed pilot pattern.

[0212] At this time, L1B_first_sub_mimo and L1D_mimo may indicate whether MIMO transmission has been applied to the corresponding subframe.

[0213] That is, even if L1B_first_sub_scattered_pilot_pattern or L1D_scattered_pilot_pattern has the same value, depending on whether it is SISO transmission or MIMO transmission, the distributed pilot pattern may be interpreted as a SISO pattern as shown in Table 1 below, or as a MIMO pattern as shown in Table 2 below.

[0214] ValueSP patternValueSP patternValueSP pattern00000SP3_201000SP12_210000Reserved00001SP3_401001SP12_4......00010SP4_201010SP16_2......00011SP4_401011SP16_4.. ....00100SP6_201100SP24_2......00101SP6_401101SP24_4......00110SP8_201110SP32_2......00111SP8_401111SP32_411111Reserved

[0215] Table 1 shows the signaling formats of L1D_scattered_pilot_pattern and L1B_first_sub_scattered_pilot_pattern for SISO.

[0216] ValueSP patternValueSP patternValueSP pattern00000MP3_201000MP12_210000Reserved00001MP3_401001MP12_4......00010MP4_201010MP16_2......00011MP4_401011MP16_4.. ....00100MP6_201100MP24_2......00101MP6_401101MP24_4......00110MP8_201110MP32_2......00111MP8_401111MP32_411111Reserved

[0217] Table 2 shows the signaling formats of L1D_scattered_pilot_pattern and L1B_first_sub_scattered_pilot_pattern for MIMO.

[0218] In Tables 1 and 2, SP represents the SISO Pilot, and MP represents the MIMO Pilot.

[0219] Ultimately, when combining LDM and MIMO technologies with existing SISO receivers in mind to transmit SISO and MIMO signals in the same subframe, both the SISO receiver and the MIMO receiver must be able to simultaneously receive accurate distributed pilot pattern information through a common signaling field, either L1B_first_sub_scattered_pilot_pattern or L1D_scattered_pilot_pattern. This implies that L1B_first_sub_scattered_pilot_pattern or L1D_scattered_pilot_pattern must be compatible with both SISO and MIMO.

[0220] For example, if L1B_first_sub_scattered_pilot_pattern or L1D_scattered_pilot_pattern is 00000, the SISO receiver must perform channel estimation using SP3_2 of Table 1, and the MIMO receiver must perform channel estimation using MP3_2 of Table 2.

[0221] In order to receive a MIMO transmission signal, it is necessary to distinguish and estimate the first polarization channel and the second polarization channel, and therefore, distinguishable pilot signals are transmitted to both the first polarization (first antenna) and the second polarization (second antenna).

[0222] The MIMO distributed pilot pattern used in ATSC 3.0 systems is defined using either Walsh-Hadamard encoding or null-pilot encoding.

[0223] The pilot pattern corresponding to Walsh-Hadamard encoding is a method in which both the first and second polarizations transmit their respective pilots at the same OFDM cell locations. That is, Walsh-Hadamard encoding is designed so that the sequence corresponding to the pilots for the first polarization and the sequence corresponding to the pilots for the second polarization are orthogonal, thereby enabling the extraction of only the corresponding pilots from each transmission channel.

[0224] The pilot pattern corresponding to the null pilot encoding is a method in which the second polarization is muted at the position where the first polarization transmits the pilot, and the first polarization is muted at the position where the second polarization transmits the pilot.

[0225] By comparing the SISO distributed pilot pattern, MIMO Walsh-Hadamard distributed pilot pattern, and MIMO null-pilot distributed pilot pattern, which are signaled with the same 5-bit value in Tables 1 and 2 above, the following relationship can be confirmed.

[0226] The first polarization (first antenna) portion of the MIMO Walsh-Hadamard distributed pilot pattern transmits pilot signals identical to those of the SISO distributed pilot pattern to the same OFDM cell location.

[0227] The first polarization (first antenna) portion of the MIMO null-pilot distributed pilot pattern transmits pilot signals at only half of the pilot locations of the SISO distributed pilot pattern.

[0228] This relationship can be summarized as shown in Table 3 below.

[0229] Pilot EncodingAlgorithmAntennaScatteredPilotSubframeBoundaryPilotCommonContinualPilotAdditionalContinualPilotEdgePilotWalsh-Hadamard#1SISOSISOSISOSISOSISO#2WHWHSISOSISO / WHWHNull Pilot#1NPSISOSISOSISO / NPSISO#2NPWHSISOSISO / NPWH

[0230] In Table 3, WH represents Walsh-Hadamard and NP represents Null Pilot.

[0231] FIGS. 6, FIGS. 7, and FIGS. 8 show the SISO scattered pilot pattern, the MIMO Walsh-Hadamard scattered pilot pattern, and the MIMO null-pilot scattered pilot pattern when the 5-bit L1B_first_sub_scattered_pilot_pattern or L1D_scattered_pilot_pattern is 00000.

[0232] Figure 6 is a diagram showing an example of a SISO distributed pilot pattern corresponding to SP3_2.

[0233] Referring to Fig. 6, D for SISO X = 3 and D Y = The pilot positions in the case of 2 can be known.

[0234] Figure 7 is a diagram showing an example of a Walsh-Hadamard encoded MIMO distributed pilot pattern corresponding to MP3_2.

[0235] Referring to Fig. 7, it can be seen that the OFDM cell locations of the SISO distributed pilot pattern corresponding to SP3_2 and the OFDM cell locations of the Walsh-Hadamard encoded MIMO distributed pilot pattern corresponding to MP3_2 are basically the same.

[0236] The Walsh-Hadamard encoded MIMO distributed pilot pattern shown in FIG. 7 transmits the same pilots shown in FIG. 6 in both group 1 positions and group 2 positions for the first polarization. At this time, for the second polarization, pilots identical to those for the first polarization are transmitted in group 1 positions, and pilots opposite in phase to those for the first polarization are transmitted in group 2 positions.

[0237] That is, in the Walsh-Hadamard encoded MIMO distributed pilot pattern shown in Fig. 7, the same pilots as the SISO distributed pilot pattern shown in Fig. 6 are transmitted in the first polarization, and in the second polarization, only some pilots are transmitted with their phases reversed at the same positions as the SISO distributed pilot pattern shown in Fig. 6.

[0238] Figure 8 is a diagram showing an example of a null-pilot encoded MIMO distributed pilot pattern corresponding to MP3_2.

[0239] Referring to Fig. 8, it can be seen that the OFDM cell locations of the Walsh-Hadamard encoded MIMO distributed pilot pattern corresponding to MP3_2 and the OFDM cell locations of the null-pilot encoded MIMO distributed pilot pattern corresponding to MP3_2 are basically the same, differing only in grouping.

[0240] However, in the null-pilot encoded MIMO distributed pilot pattern shown in FIG. 8, pilots are transmitted only at group 1 positions for the first polarization, and pilots are transmitted only at group 2 positions for the second polarization.

[0241] That is, the null-pilot encoded MIMO distributed pilot pattern shown in FIG. 8 transmits pilot signals only at half of the pilot locations (group 1 positions) of the SISO distributed pilot pattern shown in FIG. 6 during the first polarization. Similarly, the null-pilot encoded MIMO distributed pilot pattern transmits pilot signals only at the other half of the pilot locations (group 2 positions) of the SISO distributed pilot pattern shown in FIG. 6 during the second polarization.

[0242] In a broadcast signal transmission / reception system combining LDM and MIMO, the core layer and the enhanced layer may use the same pilot signal to prevent an increase in receiver complexity and reduce the burden of receiver memory usage.

[0243] A broadcast signal transmitter of the structure described in FIGS. 3 and 5 transmits a broadcast signal combining SISO and MIMO, considering a conventional single-antenna receiver, and the single-antenna receiver can receive only the first polarization signal. In such an environment, if a null-pilot pattern is applied as a distributed pilot pattern, the SISO receiver uses the interference signal transmitted from the second polarization in the corresponding PLP (Physical Layer Pipe) for pilot-based channel estimation, which may lead to misestimation.

[0244] Meanwhile, when transmitting a broadcast signal combining SISO and MIMO by combining LDM and MIMO technologies, if a null-pilot pattern is applied, it may conflict with L1-basic and L1-detail signaling for existing SISO services.

[0245] Existing ATSC 3.0 broadcast systems set the L1B_mimo_scattered_pilot_encoding field (L1-Basic signaling field) to 0 in the following two cases.

[0246] - When the Walsh-Hadamad pilot pattern is used

[0247] - If there is no MIMO-applied subframe within the transmission frame

[0248] When receiving a subframe combining SISO and MIMO by combining LDM and MIMO technologies, it may be better for the SISO receiver not to know of the existence of the enhanced layer transmitted in the form of MIMO. Therefore, in this case, L1B_first_sub_mimo (for the first subframe) or L1D_mimo (for other subframes) should be set to 0. Here, L1B_first_sub_mimo and L1D_mimo may be fields indicating whether MIMO is applied to the corresponding subframe (in principle, set to 1 if MIMO is applied). In such cases, where L1B_first_sub_mimo (for the first subframe) or L1D_mimo (for other subframes) is set to 0 despite MIMO being applied to the enhanced layer, the MIMO receiver may operate based on other MIMO-related fields other than these fields to identify the MIMO pilot pattern.

[0249] When the core layer transmits SISO signals and only the enhanced layer applies MIMO, there may not be any MIMO subframes in the transmission frame other than the subframes in which SISO and MIMO are combined in LDM, or there may be MIMO subframes in the transmission frame other than the subframes in which SISO and MIMO are combined in LDM.

[0250] If there are no MIMO subframes in the transmission frame other than the subframes in which SISO and MIMO are combined in LDM, and a null-pilot pattern is applied to the subframes in which SISO and MIMO are combined in LDM so that L1B_mimo_scattered_pilot_encoding is set to 1, then from the perspective of the existing SISO receiver, this usage is not desirable because it causes a collision with L1B_first_sub_mimo or L1D_mimo, which are set to 0 in the received preamble.

[0251] In cases where a MIMO subframe exists within a transmission frame other than subframes where SISO and MIMO are combined via LDM, signaling collisions may not occur if other MIMO subframes within the transmission frame apply a null-pilot pattern. However, even in such cases, considering the situation where a single distributed pilot pattern identification field (L1B_first_sub_scattered_pilot_pattern or L1D_scattered_pilot_pattern) is shared by the SISO receiver and the MIMO receiver, it is preferable to prohibit the use of null-pilot patterns and use only the Walsh-Hadamard pilot pattern. At this time, the Walsh-Hadamard pilot pattern may be applied to the enhanced layer of the broadcast signal transmission device of FIGS. 3 and 5, regardless of the value signaled in L1B_mimo_scattered_pilot_encoding.

[0252] Ultimately, when transmitting a broadcast signal combining SISO and MIMO by combining LDM and MIMO technologies, among null-pilot encoding and Walsh-Hadamard encoding, only Walsh-Hadamard encoding can be allowed as the pilot encoding.

[0253] At this time, the 1-bit signaling field L1B_mimo_scattered_pilot_encoding can be set to 0, which can indicate both a MIMO pilot pattern with Walsh-Hadamard encoding and the SISO pilot pattern simultaneously.

[0254] The core layer and the enhanced layer can share pilots not only when MIMO is applied to both the core layer and the enhanced layer, but also when SISO is applied to the core layer and MIMO is applied only to the enhanced layer.

[0255] Figure 9 is a diagram showing an example of a transmission signal configuration in the case where a SISO signal is transmitted through only one of two MIMO antennas.

[0256] Referring to Fig. 9, it can be seen that in the first polarization (V-POL), the core layer signal and the enhanced layer signal are transmitted together, and in the second polarization (H-POL), only the enhanced layer signal is transmitted.

[0257] The example illustrated in FIG. 9 is an example in which a Walsh-Hadamard pilot pattern is applied, and it can be seen that the dispersion pilot pattern in the first polarization (V-POL) is applied equally to the core layer and the enhanced layer. In the example illustrated in FIG. 9, the phase of the pilots in some cell positions of the second polarization (H-POL) is opposite to that of the pilots of the first polarization.

[0258] Figure 10 is a diagram showing an example of a transmission signal configuration in the case where a SISO signal is transmitted through both MIMO antennas.

[0259] Referring to FIG. 10, it can be seen that the core layer signal and the enhanced layer signal are transmitted together in the first polarization (V-POL) and the second polarization (H-POL).

[0260] The example illustrated in FIG. 10 is also an example where the Walsh-Hadamard pilot pattern is applied, and it can be seen that the dispersion pilot pattern is applied equally to the core layer and the enhanced layer in the first polarization (V-POL) and the second polarization (H-POL). In the example illustrated in FIG. 10, the phase of the pilots in some cell positions of the second polarization (H-POL) is opposite to that of the pilots of the first polarization.

[0261] Figure 11 is a diagram comparing the SISO distributed pilot pattern and the MIMO distributed pilot pattern.

[0262] Referring to Fig. 11, it can be seen that in the first polarization (V-POL), the Walsh-Hadamard encoded MP3_2 MIMO distributed pilot pattern is exactly the same as the SISO SP3_2 distributed pilot pattern. In the second polarization (H-POL), the phases of the pilots at the pilot positions corresponding to the second group are inverted.

[0263] FIG. 12 is a block diagram showing an example of a broadcast signal transmission device using multiple transmission antennas and hierarchical division multiplexing.

[0264] Referring to FIG. 12, a broadcast signal transmission device using multiple transmission antennas and layered division multiplexing according to an embodiment of the present invention includes a core layer MIMO signal generation unit (1110), an enhanced layer MIMO signal generation unit (1120), an LDM coupling unit (1130), an L1 signaling generation unit (1140), and a transmission signal generation unit (1150).

[0265] The core layer MIMO signal generation unit (1110) generates core layer MIMO signals.

[0266] At this time, the core layer MIMO signal generation unit (1110) may include a core layer FEC (Forward Error Correction) encoder (1111), a core layer bit-interleaver (1112), a core layer MIMO demultiplexer (DEMUX) (1113), core layer symbol mappers (1114, 1115), and a core layer MIMO precoder (1116).

[0267] The core layer FEC encoder (1111) can generate bit groups, such as FEC frames (FEC packets), by applying channel coding to baseband packets corresponding to the core layer. At this time, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding.

[0268] The core layer bit-interleaver (1112) can perform bit interleaving on FEC frames output from the core layer FEC encoder (1111).

[0269] The core layer MIMO demux (1113) and core layer symbol mappers (1114, 1115) can generate data cells for delivering output to each of the multiple antennas for the output bit sequence of the core layer bit-interleaver (1112). That is, the core layer MIMO demux (1113) can group the input bit sequence according to the modulation order and the number of multiple antennas to convert the input bit sequence into data cells. In this case, the core layer MIMO demux (1113) can map even-indexed bits from the bit-interleaved FEC-encoded bit stream to the first antenna (polarization) and odd-indexed bits to the second antenna (polarization). In this case, the bit sequence corresponding to each group may vary depending on the modulation order and the number of multiple antennas. Core layer symbol mappers (1114, 1115) map the output of the core layer MIMO demultiplexer (1113) to constellations corresponding to groups of bits corresponding to each antenna (polarization) output, and generate data cells corresponding to each antenna output. In one embodiment, even-numbered bits in the bit group may be mapped to data cells for the first antenna (ANTENNA 1), and odd-numbered bits may be mapped to data cells for the second antenna (ANTENNA 2). At this time, the grouping of each bit or the constellation mapping of bits utilizing this in the core layer symbol mappers (1114, 1115) may also be performed using various methods not exemplified.

[0270] Groups of two different data cells are input to a core layer MIMO precoder (1116). At this time, the core layer MIMO precoder (1116) can perform signal processing for spatial multiplexing and can adjust the first antenna (polarization) signal and the second antenna (polarization) signal at the OFDM cell level (constellation symbol level).

[0271] At this time, the core layer MIMO precoder (1116) may include a streaming combiner, an IQ polarization interleaving unit, and a phase hopping unit. At this time, the streaming combiner can combine two data cells entering as input and output. At this time, the IQ polarization interleaving unit can exchange the quadrature components of two data cells entering as input and output. At this time, the phase hopping unit can change the phase of the data cells entering as input and output. At this time, all three sub-blocks may be activated and operating, all may be deactivated and operating, or only some blocks may be activated and operating. Additionally, depending on the channel coding rate and modulation order applied to the data cells entering as input to each sub-block, each sub-block may output different signals or output the same signal. The core layer MIMO precoder (1116) illustrated in FIG. 12 can output two data cells to be output through the first antenna (ANTENNA 1) and the second antenna (ANTENNA 2). That is, two output signals are produced from the core layer MIMO signal generator (1110), one of which is a signal for transmission using the first antenna (ANTENNA 1), and the other is a signal for transmission using the second antenna (ANTENNA).

[0272] The first antenna (ANTENNA 1) and the second antenna (ANTENNA 2) may correspond to the first polarization and the second polarization. That is, the first antenna (ANTENNA 1) may correspond to the first polarization, and the second antenna (ANTENNA 2) may correspond to the second polarization. For example, the first polarization may be vertical polarization, and the second polarization may be horizontal polarization.

[0273] In this case, polarization can be the orientation of the electric field vector of a radiated electromagnetic wave with respect to the horizon as seen from the antenna. That is, polarization can describe the orientation of the wave emitted from. This orientation can be planar or circular.

[0274] In the following, the first antenna may be replaced with the first polarization, and the second antenna may be replaced with the second polarization.

[0275] The enhanced layer MIMO signal generation unit (1120) generates enhanced layer MIMO signals.

[0276] At this time, the enhanced layer MIMO signal generation unit (1120) may include an enhanced layer FEC (Forward Error Correction) encoder (1121), an enhanced layer bit-interleaver (1122), an enhanced layer MIMO demultiplexer (DEMUX) (1123), enhanced layer symbol mappers (1124, 1125), and an enhanced layer MIMO precoder (1126).

[0277] The enhanced layer FEC encoder (1121) can generate bit groups, such as FEC frames (FEC packets), by applying channel coding to baseband packets corresponding to the enhanced layer. At this time, the channel coding may be a single-structure method or a method composed of multiple stages, such as internal and external coding.

[0278] The enhanced layer bit-interleaver (1122) can perform bit interleaving on FEC frames output from the enhanced layer FEC encoder (1121).

[0279] The enhanced layer MIMO demux (1123) and enhanced layer symbol mappers (1124, 1125) can generate data cells for delivering output to each of the multiple antennas for the output bit sequence of the enhanced layer bit-interleaver (1122). That is, the enhanced layer MIMO demux (1123) can group the input bit sequence according to the modulation order and the number of multiple antennas to convert the input bit sequence into data cells. In this case, the enhanced layer MIMO demux (1123) can map even-indexed bits from the bit-interleaved FEC-encoded bit stream to the first antenna (polarization) and odd-indexed bits to the second antenna (polarization). In this case, the bit sequence corresponding to each group may vary depending on the modulation order and the number of multiple antennas. Enhanced layer symbol mappers (1124, 1125) map the output of the enhanced layer MIMO demux (1123) to constellations corresponding to groups of bits corresponding to each antenna (polarization) output, and generate data cells corresponding to each antenna output. In one embodiment, even-numbered bits in the bit group may be mapped to data cells for the first antenna (ANTENNA 1), and odd-numbered bits may be mapped to data cells for the second antenna (ANTENNA 2). At this time, the grouping of each bit or the constellation mapping of bits utilizing this in the enhanced layer symbol mappers (1124, 1125) may also be performed using various methods not exemplified.

[0280] Groups of two different data cells are input to an enhanced layer MIMO precoder (1126). At this time, the enhanced layer MIMO precoder (1126) can perform signal processing for spatial multiplexing and can adjust the first antenna (polarization) signal and the second antenna (polarization) signal at the OFDM cell level (constellation symbol level).

[0281] At this time, the enhanced layer MIMO precoder (1126) may include a streaming combiner, an IQ polarization interleaving unit, and a phase hopping unit. At this time, the streaming combiner can combine two data cells entering as input and output. At this time, the IQ polarization interleaving unit can exchange the quadrature components of two data cells entering as input and output. At this time, the phase hopping unit can change the phase of the data cells entering as input and output. At this time, all three sub-blocks may be activated and operating, all may be deactivated and operating, or only some blocks may be activated and operating. Additionally, depending on the channel coding rate and modulation order applied to the data cells entering as input to each sub-block, each sub-block may output different signals or output the same signal. The enhanced layer MIMO precoder (1126) illustrated in FIG. 12 can output two data cells to be output through the first antenna (ANTENNA 1) and the second antenna (ANTENNA 2). That is, two output signals are produced from the enhanced layer MIMO signal generator (1120), one of which is a signal for transmission using the first antenna (ANTENNA 1), and the other is a signal for transmission using the second antenna (ANTENNA).

[0282] At this time, the core layer MIMO signals are generated based on core layer MIMO precoding, and the enhanced layer MIMO signals can be generated based on enhanced layer MIMO precoding.

[0283] At this time, the core layer MIMO precoding and the enhanced layer MIMO precoding can each be performed using one or more of stream combining, IQ polarization interleaving, and phase hopping.

[0284] At this time, whether stream combining is enabled can be signaled by the 1-bit L1D_plp_mimo_stream_combining field included in the L1 detail signaling field.

[0285] At this time, whether IQ polarization interleaving is enabled can be signaled by the 1-bit L1D_plp_mimo_IQ_interleaving field included in the L1 detail signaling field.

[0286] At this time, whether phase hopping is enabled can be signaled by the 1-bit L1D_plp_mimo_PH field included in the L1 detail signaling field.

[0287] At this time, if the IQ polarization interleaving corresponding to the core layer is activated, the IQ polarization interleaving corresponding to the enhanced layer can be activated.

[0288] At this time, if phase hopping corresponding to the core layer is activated, phase hopping corresponding to the enhanced layer may be activated.

[0289] At this time, the stream combining, the IQ polarization interleaving, and the phase hopping may correspond to the first MIMO field, the second MIMO field, and the third MIMO field, respectively.

[0290] At this time, the second MIMO field corresponding to the core layer and the second MIMO field corresponding to the enhanced layer are set identically, and the third MIMO field corresponding to the core layer and the third MIMO field corresponding to the enhanced layer can be set identically.

[0291] The LDM coupling unit (1130) performs layered division multiplexing on the core layer MIMO signals and the enhanced layer MIMO signals to generate a first superposition signal (first polarization signal) corresponding to the first polarization and a second superposition signal (second polarization signal) corresponding to the second polarization.

[0292] At this time, the LDM coupling part (1130) may include injection level controllers (1131, 1132), couplings (1133, 1134) and power normalizers (1135, 1136).

[0293] That is, through the LDM coupling section, the transmission power of the enhanced layer MIMO signals for the first antenna (ANTENNA 1) and the second antenna (ANTENNA 2) is adjusted in injection level controllers (1131, 1132) according to a predetermined power injection level (IL). At this time, the power of the enhanced layer MIMO signal for the first antenna (ANTENNA 1) is adjusted through the injection level controller (1131), and the power of the enhanced layer MIMO signal for the second antenna (ANTENNA 2) is adjusted through the injection level controller (1132).

[0294] Therefore, two injection levels are used in the LDM coupling part (1130) shown in Fig. 12.

[0295] At this time, the injection levels can each represent the power ratio of the enhanced layer relative to the core layer, and information for signaling the injection levels can be included in the L1 signaling fields.

[0296] The enhanced layer MIMO signal for the power-adjusted first antenna (ANTENNA 1) is added to the core layer MIMO signal for the first antenna (ANTENNA 1) by the combiner (1133), and the enhanced layer MIMO signal for the power-adjusted second antenna (ANTENNA 2) is added to the core layer MIMO signal for the second antenna (ANTENNA 2) by the combiner (1134).

[0297] The signal added through the combiner (1133) is output as a first superposition signal (first polarization signal) after undergoing power normalization by the power normalizer (1135), and the signal added through the combiner (1134) is output as a second superposition signal (second polarization signal) after undergoing power normalization by the power normalizer (1136).

[0298] The transmission signal generation unit (1150) generates a first polarization transmission signal including a first preamble corresponding to the first polarization and a second polarization transmission signal including a second preamble corresponding to the second polarization.

[0299] At this time, the transmission signal generation unit (1150) includes framing & interleaving units (1151, 1152) and waveform generators (1153, 1154).

[0300] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (1151) on the first superposition signal output through the power normalizer (1135). The output of the framing & interleaving unit (1151) is input to the waveform generator (1153) and output to the first antenna as a first polarization transmission signal.

[0301] Time interleaving, frame generation (including preamble), and frequency interleaving can be performed in the framing & interleaving unit (1152) on the second superposition signal output through the power normalizer (1136). The output of the framing & interleaving unit (1152) is input to the waveform generator (1154) and output to the second antenna as a second polarization transmission signal.

[0302] The framing and interleaving units (1151, 1152) illustrated in FIG. 12 can each generate a signal corresponding to a frame to be transmitted through an antenna using data cells that are input. At this time, the framing and interleaving units (1151, 1152) may or may not perform time interleaving with the input data cells. At this time, the framing and interleaving units (1151, 1152) may perform framing by configuring a preamble symbol and a subframe with respect to the data cells. At this time, the preamble symbol may not include the data cells. At this time, frequency interleaving may or may not be applied with the activation.

[0303] Grouped data cells, which are the outputs of the framing and interleaving units (1151, 1152), are input to waveform generators (1153, 1154). At this time, the waveform generators (1153, 1154) can each perform an Inverse Fast Fourier Transform (IFFT) through pilot insertion and insert a Guard Interval symbol. Additionally, the waveform generators (1153, 1154) can each generate a bootstrap symbol and output it by placing it at the very beginning of the transmission frame. At this time, each of the waveform generators (1153, 1154) may enable or disable the Multiple-Input Single-Output (MISO) signal processing function.

[0304] The L1 signaling generation unit (1140) can generate injection level signaling information regarding two injection levels corresponding to the enhanced layer MIMO signals.

[0305] That is, injection level information (IL INFO) for an enhanced layer MIMO signal for a first antenna (or polarization) and injection level information (IL INFO) for an enhanced layer MIMO signal for a second antenna (or polarization) are used in injection level controllers (1131, 1132) and are also transmitted to and used by power normalizers (1135, 1136). At this time, the power normalizers (1135, 1136) each adjust the power of the input signal to an appropriate level by multiplying the magnitude of the combined signal by a normalizing factor calculated from the injection level information.

[0306] At this time, injection level information (IL INFO) for an enhanced layer MIMO signal for the first antenna (or polarization) and injection level information (IL INFO) for an enhanced layer MIMO signal for the second antenna (or polarization) are transmitted to an L1 signaling generation unit (1140) to generate L1 signaling information to be included in a preamble and transmitted. That is, the injection level signaling information included in the L1 signaling information is included in a preamble in the framing & interleaving units (1135, 1136), modulated, and transmitted.

[0307] At this time, since there are two injection level controllers (1131, 1132), there are two injection levels used, and there are also two preambles generated in the framing and interleaving sections (1151, 1152).

[0308] The injection levels of the injection level controllers (1131, 1132) may be set to the same injection level or to different injection levels.

[0309] The first preamble generated in the framing & interleaving unit (1151) and the second preamble generated in the framing & interleaving unit (1152) may each include only the first injection level information (when the injection levels of the injection level controllers (1131, 1132) are the same), or they may include both the first injection level information and the second injection level information (when the injection levels of the injection level controllers (1131, 1132) are different). In this case, the first injection level signaling information included in the first preamble and the first injection level signaling information included in the second preamble may be the same. Likewise, the second injection level signaling information included in the first preamble and the second injection level signaling information included in the second preamble may be the same. Furthermore, the entire L1 signaling information included in the first preamble may be identical to the entire L1 signaling information included in the second preamble. That is, the first preamble transmitted for the first polarization and the second preamble transmitted for the second polarization may be configured identically by being composed of the same modulation signals, and the transmission power may be the same or different.

[0310] At this time, the first preamble and the second preamble may include identical 5-bit injection level signaling information corresponding to the injection levels.

[0311] The enhanced layer MIMO signal for the first antenna / polarization and the enhanced layer MIMO signal for the second antenna / polarization may have their power adjusted to correspond to the same injection level or to correspond to different injection levels.

[0312] At this time, the first preamble corresponding to the first antenna (polarization) and the second preamble corresponding to the second antenna (polarization) may include the same 5-bit injection level field (L1D_plp_ldm_injection_level).

[0313] At this time, the injection level controllers (1131, 1132) and power normalizers (1135, 1136) illustrated in FIG. 12 can all operate based on an injection level corresponding to the same 5-bit injection level field (L1D_plp_ldm_injection_level). That is, the same injection level value can be shared for the first antenna (polarization) and the second antenna (polarization).

[0314] According to the embodiment, different injection levels may be used for the first antenna / polarization and the second antenna / polarization. In this case, if the L1-Detail signaling for the first antenna / polarization and the L1-Detail signaling for the second antenna / polarization are the same, a signaling field separate from the aforementioned 5-bit injection level field (L1D_plp_ldm_injection_level) may be required. In this case, an injection level corresponding to L1D_plp_ldm_injection_level may be used for the first antenna (polarization), and an injection level corresponding to a different signaling field may be used for the second antenna (polarization).

[0315] The LDM coupling unit (1130) illustrated in FIG. 12 and the LDM coupling unit (330) illustrated in FIG. 3 can output a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization. At this time, the LDM coupling unit (1130) illustrated in FIG. 12 and the LDM coupling unit (330) illustrated in FIG. 3 may correspond to a subframe signal generation unit.

[0316] Furthermore, for the Non-MIMO (SISO) subframe described later, the subframe signal generation unit may correspond to a MIMO signal generation unit (structure identical to 1110 or 1120 in FIG. 12) that generates the output of a MIMO precoder as a first polarization signal and a second polarization signal in a MIMO transmission structure according to the existing ATSC 3.0 standard. In this case, the first polarization signal and the second polarization signal, which are the outputs of the MIMO precoder, may be input to a first framing & interleaving unit and a second framing & interleaving unit, respectively. At this time, since the MIMO precoder may be disabled, the first polarization signal may be the output of the core layer symbol mapper (114) or the enhanced layer symbol mapper (124), and the second polarization transmission signal may be the output of the core layer symbol mapper (115) or the enhanced layer symbol mapper (125). At this time, the output of the first framing & interleaving unit may be input to the first waveform generator, and the output of the second framing & interleaving unit may be input to the second waveform generator. At this time, the output of the first waveform generator may become the first polarization transmission signal, and the output of the second waveform generator may become the second polarization transmission signal. At this time, the first framing & interleaving unit, the second framing & interleaving unit, the first waveform generator, and the second waveform generator may constitute a transmission signal generation unit. In this way, existing MIMO transmission methods that are not LDM-compliant can be referred to as single-layer MIMO transmission.

[0317] A transmission method in which LDM and MIMO are not applied together (layered MIMO) or non-LDM MIMO is not applied, and a transmission signal is generated through a single transmission chain (going through a transmission signal generation process such as single antenna transmission), may be referred to as a Non-MIMO or SISO method. In this case, SISO may include MISO (Multiple-Input Single-Output) and SIMO (Single-Input Multiple-Output) methods.

[0318] That is, the subframe signal generation unit can output a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization.

[0319] The transmission signal generating unit (1150) illustrated in FIG. 12 and the transmission signal generating unit (340) illustrated in FIG. 3 are a first subframe indicator set (S) for the first polarization. M,0 Based on ), a first polarization transmission signal corresponding to the first polarization signal is generated, and a second subframe indicator set (S) for the second polarization is generated. M,1 A second polarization transmission signal corresponding to the second polarization signal can be generated based on the above. In this case, the transmission signal generation unit may include the aforementioned first framing & interleaving unit, second framing & interleaving unit, first waveform generator, and second waveform generator in the case of a Non-MIMO subframe.

[0320] At this time, at least one of the first polarization transmission signal and the second polarization transmission signal may include a preamble.

[0321] The subframes described in the present invention may be one of the following four types.

[0322] 1) Non-MIMO subframe

[0323] A Non-MIMO (or SISO) subframe refers to a subframe to which MIMO is not applied, and can refer to a transmission method that allows reception with a single receiving antenna because Spatial Multiplexing (SM) or Polarization Multiplexing (PM) is not applied. In this case, the Non-MIMO subframe may correspond to a SISO transmission signal and a MISO (Multiple-Input Single-Output) transmission signal.

[0324] 2) MIMO Subframe

[0325] A MIMO subframe is a MIMO subframe corresponding to the existing ATSC 3.0 standard, and may refer to a Single Layer (SL) MIMO subframe to which Layered Division Multiplexing (LDM) is not applied. That is, a MIMO subframe may correspond to the MIMO transmitter structure of the existing ATSC 3.0 standard.

[0326] 3) Type 1 Layered MIMO Subframe

[0327] The first type layered MIMO subframe may correspond to a transmitter structure in which MIMO is applied to both the core layer and the enhanced layer. That is, the first type layered MIMO subframe may correspond to the transmitter structure illustrated in FIG. 12.

[0328] 4) Type 2 Layered MIMO Subframe

[0329] The second type layered MIMO subframe may correspond to a transmitter structure in which SISO is applied to the core layer and MIMO is applied to the enhanced layer. That is, the second type layered MIMO subframe may correspond to the transmitter structure illustrated in FIGS. 3 and FIGS. 5.

[0330] At this time, the transmission signal generating unit (1150) illustrated in FIG. 12 and the transmission signal generating unit (340) illustrated in FIG. 3 are the scaling coefficient (K) of the first polarization. m Using [0]), a first polarization transmission signal corresponding to the first polarization signal is generated, and the scaling coefficient (K) of the second polarization is used. m [1]) can be used to generate a second polarization transmission signal corresponding to the second polarization signal.

[0331] At this time, the scaling coefficient of the first polarization and the scaling coefficient of the second polarization may correspond to the injection level of the hierarchical partitioning multiplexing.

[0332] At this time, the scaling coefficient (K) of the first polarization above m [0]) corresponds to a polarization index of 0, and the scaling coefficient (K of the second polarization) m [1]) can correspond to the polarization index 1.

[0333] At this time, the scaling coefficient of the first polarization and the scaling coefficient of the second polarization are applied to values ​​corresponding to complex modulation values ​​that are not set per polarization for the preamble, and may be applied to values ​​corresponding to complex modulation values ​​that are set per polarization for at least one subframe.

[0334] At this time, for the first polarization, the power of the preamble symbol corresponding to the preamble may reference the data symbol power of the first subframe that activates the first polarization.

[0335] At this time, for the second polarization, the power of the preamble symbol corresponding to the preamble may refer to the data symbol power of the first subframe that activates the second polarization.

[0336] At this time, the scaling coefficients of the first polarization and the second polarization can be applied to power scaling performed in the IFFT (Inverse Fast Fourier Transform) step.

[0337] At this time, the LDM coupling unit may hierarchically divide multiplex one of the core layer signal and the enhanced layer MIMO signals to output the first polarization signal, and output the other of the enhanced layer MIMO signals as is as the second polarization signal.

[0338] At this time, the scaling factor of the first polarization can be maintained the same even if the injection level corresponding to the hierarchical partitioning multiplexing changes.

[0339] At this time, the scaling factor of the second polarization may change as the injection level corresponding to the layered division multiplexing changes (second type layered MIMO).

[0340] At this time, the scaling factor of the second polarization may decrease as the injection level corresponding to the hierarchical division multiplexing increases.

[0341] At this time, the first subframe indicator set (S M,0 ) is a set of subframe numbers of subframes that activate the first polarization, and the second subframe indicator set (S M,1 ) may be a set of subframe numbers of subframes that activate the second polarization above.

[0342] In this case, if all subframes within the frame use MIMO (Multiple-Input Multiple-Output) or layered MIMO, the first subframe indicator set and the second subframe indicator set are each greater than or equal to 0 and N SF Less than (N SF ) can include all integers (number of subframes within the above frame).

[0343] At this time, if the second polarization is disabled while the first polarization transmits at least one SISO subframe, the first subframe indicator set is greater than or equal to 0 and N SF Less than (N SF The number of subframes within the frame) includes all integers, and the second set of subframe indicators may consist of the subframe numbers that use MIMO or layered MIMO.

[0344] At this time, if the first polarization and the second polarization are both activated during the subframe duration using SISO, the first subframe indicator set and the second subframe indicator set are each greater than or equal to 0 and N SF Less than (N SF ) can include all integers (number of subframes within the above frame).

[0345] At this time, if the first polarization and the second polarization are activated together during the subframe duration using SISO, the complex modulation value for the first polarization corresponding to the SISO subframe and the complex modulation value for the second polarization may be the same.

[0346] At this time, the first polarization transmission signal is generated using the scaling coefficient of the first polarization, and the second polarization transmission signal can be generated using the scaling coefficient of the second polarization.

[0347] At this time, the scaling coefficient of the first polarization and the scaling coefficient of the second polarization are applied to values ​​corresponding to complex modulation values ​​that are not set per polarization for the preamble, and may be applied to values ​​corresponding to complex modulation values ​​that are set per polarization for at least one subframe.

[0348] At this time, for the second polarization, the power of the preamble symbol corresponding to the preamble may refer to the data symbol power of the first subframe that activates the second polarization.

[0349] In this case, for an SISO subframe in which the first polarization and the second polarization are activated together, the scaling factor of the second polarization may correspond to a power level that is maintained equally for all physical layer pipes within the subframe.

[0350] At this time, in the case of a second type layered MIMO subframe, the scaling factor of the second polarization may correspond to an injection level that is maintained equally for all enhanced layer physical layer pipes within the subframe.

[0351] At this time, in the case of a MIMO subframe or a first-type layered MIMO subframe, the scaling factor of the second polarization may correspond to a power level that is maintained equally for all combined physical layer pipes within the subframe. At this time, the combined physical layer pipe may be a unit formed by LDM combining a core layer physical layer pipe and an enhanced layer physical layer pipe.

[0352] FIG. 13 is a diagram showing a physical layer frame of a broadcast signal according to an embodiment of the present invention.

[0353] Referring to FIG. 13, it can be seen that the physical layer frame of a broadcast signal according to one embodiment of the present invention has a structure in which bootstrap, preamble, and data subframes are connected in a time-series manner.

[0354] In particular, data within the physical layer frame illustrated in FIG. 13 can be transmitted using multiple data subframes.

[0355] A broadcast signal transmitter for MIMO transmission has a MIMO exciter that outputs two polarization transmission signals (a first polarization transmission signal and a second polarization transmission signal), and each polarization transmission signal can be output through a power amplifier. That is, the two polarization transmission signals can be output through two power amplifiers.

[0356] The polarization transmission signals, which are the outputs of the MIMO exciters corresponding to each of the two MIMO transmitting antennas (polarizations), may correspond to bootstrap and preamble signals of the same configuration, and the output powers of the polarization transmission signals may be different. Furthermore, the transmission powers of the two power amplifiers through which each of the polarization transmission signals passes may also be set differently.

[0357] At this time, setting the transmission power of the second polarization (second antenna) to a low level may help ensure successful decoding of the core layer data (legacy service) of the first polarization (first antenna).

[0358] In this case, the data subframes of the first polarization transmission signal and the second polarization transmission signal may be composed of signals of different forms. That is, the data transmitted through the first polarization and the data transmitted through the second polarization may be different from each other.

[0359] In this case, the first polarization can correspond to a general Layered Division Multiplexing (LDM) configuration having both a core layer and an enhanced layer, whereas the second polarization can have a unique configuration having only an enhanced layer without a core layer.

[0360] To support such a unique structure, appropriate power scaling corresponding to each polarization may be required in the IFFT block within the waveform generator.

[0361] FIG. 14 is a diagram showing broadcast signal frames transmitted to two MIMO antennas according to an embodiment of the present invention.

[0362] Referring to FIG. 14, it can be seen that the power of the enhanced layer signal (ANT1 SIG.) of the first antenna (TRANSMIT ANTENNA #1, first polarization) and the power of the enhanced layer signal (ANT2 SIG.) of the second antenna (TRANSMIT ANTENNA #2, second polarization) are the same.

[0363] In this case, in the example illustrated in FIG. 14, the first antenna (TRANSMIT ANTENNA #1, first polarization) and the second antenna (TRANSMIT ANTENNA #2, second polarization) can use the L1D_plp_ldm_injection_level field in common.

[0364] For convenience of explanation, the bootstrap and preamble are shown together in FIG. 14, but as previously mentioned, the bootstrap and preamble can be transmitted sequentially.

[0365] As a result, the transmission power of the first polarization transmission signal and the second polarization transmission signal can be set differently from each other.

[0366] At this time, the first polarization transmission signal and the second polarization transmission signal may pass through the first power amplifier and the second power amplifier, respectively. At this time, the first polarization transmission signal and the second polarization transmission signal, having passed through the power amplifiers, may be output with different transmission powers to the transmission line physically connected to transmitting antenna 1 and the transmission line physically connected to transmitting antenna 2, respectively.

[0367] At this time, the ratio between the output power of the first polarization transmission signal and the output power of the second polarization transmission signal can be determined in correspondence with the L1D_plp_ldm_injection_level field.

[0368] That is, when setting the transmission power of the first polarization transmission signal and the transmission power of the second polarization transmission signal in waveform generators, the L1D_plp_ldm_injection_level field can be taken into account.

[0369] The waveform generators illustrated in FIGS. 1, 2, 3, or 12 may include an IFFT block. In particular, for the IFFT block, the baseband time domain signal after IFFT can be expressed as Equation 1 below for each of the first polarization and the second polarization.

[0370] [Mathematical Formula 1]

[0371]

[0372] That is, the above mathematical formula 1 represents the post-IFFT signal description.

[0373] Ψ in the above mathematical formula 1 l,k (t) can be expressed as in Equation 2 below, and Ψ m,l,k (t) can be expressed as in Equation 3 below. In this case, Ψ l,k (t) and Ψ m,l,k (t) may be the same as the values ​​defined in the existing ATSC 3.0 A / 322 standard.

[0374] [Mathematical Formula 2]

[0375]

[0376] [Mathematical Formula 3]

[0377]

[0378] In this case, a can represent a polarization (antenna) index. In this case, a can be set to 0 for the first polarization and a can be set to 1 for the second polarization.

[0379] In this case, k can represent the carrier number.

[0380] In this case, l can represent an OFDM symbol number starting from 0 for the first preamble symbol of a frame and being reset at the first OFDM symbol of each subframe.

[0381] In this case, m is 0 ≤ m < N SF It can represent the subframe number.

[0382] At this time, c l,k can be the complex modulation value for carrier k of the preamble symbol number l.

[0383] At this time, c a,m,l,k may be the complex modulation value for carrier k of the OFDM symbol number l in subframe number m associated with polarization a.

[0384] At this time, K m [a] may be a scaling coefficient subject to subframe number m and antenna index a. That is, the scaling coefficient K m[a] can vary depending on the antenna index and the subframe. In this case, the scaling factor K m [a] can be maintained identically within one subframe, and thus, in the case of a second type layered MIMO subframe, the injection level can be maintained identically within one subframe.

[0385] At this time, K m The value of [a] may be related to injection level information as summarized in Table 4 below.

[0386] Antenna-Specific Injection Level of EL below CL [dB]K m[a]Type AType Ba= 0, 1a= 0a= 10.01.00000001.00000000.70710680.51.00000001.00000000.68647611.01.00000001.00000000.66534831.51.00000001.00000000.64381782.01.00000001.00000000.62198322.51.00000001.0000000.59994583.01.00000001.00000000.57780673.51.00000001.00000000.55 566524.01.00000001.00000000.5336174.51.00000001.00000000.51175285.01.00000001.00000000.49015616.01.00000001.00000000.44806257.01.00000001.0000000.40784508.01.00000001.00000000.36987429.01.00000001.00000000.334388710.01.000000001.00000000 .301511411.01.00000001.00000000.271270312.01.00000001.00000000.243620413.01.00000001.00000000.218464414.01.00000001.00000000.195669315.01.00000001.00000000.175081216.01.00000001.0000000.156535517.01.00000001.00000000.139865318.01.00000 001.00000000.124906619.01.00000001.00000000.111502120.01.00000001.00000000.099503721.01.00000001.00000000.088773222.01.00000001.00000000.079183423.01.00000001.0000000.070617924.01.00000001.0000000.062970525.01.00000001.0000000.0561454

[0387] That is, Table 4 shows the scaling coefficient according to the injection level of the injection layer when LDM and MIMO are used together.

[0388] At this time, in Table 4 above, Type A corresponds to the transmitter structure shown in FIG. 12 (or FIG. 2 and FIG. 4), and Type B corresponds to the transmitter structure shown in FIG. 3 and FIG. 5.

[0389] In this case, the IFFT output of Equation 1 above may correspond to the case where all frames use a combined LDM and MIMO technique. If a subframe corresponding to the combination of LDM and MIMO is time division multiplexed with a subframe to which LDM and MIMO are not applied together, the IFFT processing may need to be expressed differently.

[0390] At this time, NoC P,l is (l+ 1) th The number of carriers in the preamble symbol (the number of carriers in the (l+ 1) th It can represent a preamble symbol. The first preamble symbol (l=0) always has a minimum NoC, and subsequent preamble symbols (0 <l<L Fp ) can share the same NoC value that is signaled in L1-Basic.

[0391] At this time, NoC m can represent the number of carriers of subframe m.

[0392] At this time, L SFm can represent the number of data and subframe boundary symbols in subframe m.

[0393] At this time, L Fp can represent the number of OFDM symbols in the preamble.

[0394] At this time, N SF can represent the number of subframes in a frame.

[0395] In this case, P'preamble,a,l is (l + 1) derived from the input of the IFFT block related to polarization a (before scaling by K0[a]). th The frequency domain total power of the preamble symbol (the frequency domain total power of the (l + 1) th It can represent the preamble symbol, derived from the input to the IFFT block (before scaling by K0[a]) associated with polarization a). In this case, P'preamble,a,l is P as defined in the existing ATSC 3.0 A / 322 standard. preamble,l It can share the same value as. For polarization a, (l + 1) th The power of the preamble symbol is scaled by K0[a] (K0[a]) 2 It can be adjusted to P'preamble,a,l.

[0396] At this time, P' data,a,mcan represent the frequency domain total power of each data and subframe boundary symbol in subframe m, derived from the input to the IFFT block associated with polarization a. In this case, P' data,a,m is P defined in the existing ATSC 3.0 A / 322 standard data,m It can share the same value as. With respect to the data and subframe boundary symbols transmitted from polarization a, the power of subframe m is scaled by K0[a] (K m [a]) 2 P' data,a,m It can be adjusted.

[0397] In this case, k' can represent the carrier index relative to the center frequency. That is, k' can be k - (NoC - 1) / 2.

[0398] At this time, T sm can represent the total symbol duration of each data and subframe boundary symbol in subframe m. In this case, T Sm = T Um + T Gm It could be.

[0399] At this time, T UmIt can represent the useful symbol duration for each data and subframe boundary symbol in subframe m.

[0400] At this time, T Gm It can represent the duration of the guard interval for each data and subframe boundary symbol in subframe m including extra samples for each data and subframe boundary symbol.

[0401] At this time, T BS can represent the duration of the bootstrap.

[0402] At this time, T P can represent the total duration of the preamble. In this case, T P = L Fp T Sp It could be.

[0403] At this time, T Sp can represent the total symbol duration of each preamble symbol. In this case, T Sp = T Up + T Gp It could be.

[0404] At this time, T Upcan represent the useful symbol duration for each preamble symbol.

[0405] At this time, T Gp It can represent the duration of the guard interval for each preamble symbol.

[0406] At this time, T SFm can represent the total duration of all data and subframe boundary symbols in subframe m.

[0407] At this time, ∑T SFm can represent the summation of the total duration of subframes from 0 to m-1.

[0408] The generation of baseband time-domain signals can be performed concurrently for each polarization stream. Each polarization stream can transmit different complex modulation values ​​at the same cell position. Therefore, antenna-specific notation c a,m,l,k This can be used.

[0409] Complex modulation values ​​c obtained from previous function blocks l,k and c a,m,l,k Given this, the IFFT blocks are scalar coefficients K m Power scaling can be performed based on [a].

[0410] Allowed K m Correlation between the values ​​of [a] and the injection level (allowed values ​​of K m[a] and the correspondence to the injection level) are expressed in Table 4 above. In particular, excluding the second polarization (a=1) of Type B in Table 4, all K m [a] can be given as 1(unity).

[0411] In this case, the IFFT power normalization is the average power of the baseband time domain signal (K for polarization a and subframe m). m [a]) 2 It can be normalized. In this case, for the preamble, the average power is (K0[a]) 2 It can be normalized. This power normalization applies the IFFT power normalization factor 1 / √P'preamble,a,l to the preamble and the IFFT power normalization factor 1 / √P' to the data and subframe boundary symbols. data,a,m It can be achieved by applying.

[0412] Frequency domain power parameters P'preamble, a, l and P' data,a,m is K m [a] Carrier signals not scaled to (e.g., c l,k and c a,m,l,k It can be derived from ).

[0413] Parameters not explicitly defined here may be used as defined in the existing ATSC 3.0 A / 322 standard.

[0414] In MIMO transmission, even at the same OFDM cell location, the values ​​corresponding to the data cells (and cells of the subframe boundary symbol) transmitted by the first polarization and the second polarization are different from each other. Therefore, the IFFT power normalization factor reflected in the IFFT process during MIMO transmission can be calculated based on the frequency domain total power per polarization.

[0415] A MIMO transmitter can transmit a MIMO-applied subframe (MIMO subframe) and a SISO transmission-based subframe (Non-MIMO subframe) by multiplexing them in a Time Division Multiplexing (TDM) manner within a single transmission frame.

[0416] At this time, the transmission frame transmitted from the MIMO transmitter may be one of two types: i) a pure MIMO frame in which all subframes adopt the MIMO method, and ii) a TDM-based frame in which SISO subframes and MIMO subframes coexist.

[0417] When a SISO signal is transmitted from a MIMO transmitter according to the existing ATSC 3.0 A / 322 standard, the following two methods can be used.

[0418] - In the SISO subframe interval, the SISO signal is transmitted only at the first polarization, and the second polarization is disabled during that interval.

[0419] - In the SISO subframe interval, the SISO signal is transmitted through both the first and second polarizations.

[0420] FIG. 15 is a diagram showing an example in which, in a SISO subframe section, the SISO signal is transmitted only at the first polarization and the second polarization is disabled in that section.

[0421] Referring to Fig. 15, it can be seen that the second polarization (ANT2) is muted during the interval where a Non-MIMO subframe is transmitted through the first polarization (ANT1).

[0422] That is, in the example of Fig. 15, the first polarization transmits SISO subframes and the second polarization is disabled during that time.

[0423] FIG. 16 is a diagram showing an example in which a SISO signal is transmitted through both the first polarization and the second polarization in the SISO subframe section.

[0424] Referring to FIG. 16, it can be seen that the same Non-MIMO subframe is transmitted through both the first polarization (ANT1) and the second polarization (ANT2).

[0425] That is, in the example of Fig. 16, the first polarization and the second polarization transmit the same signal copies of SISO subframes.

[0426] In the following, a waveform generation method encompassing both cases of FIG. 15 and FIG. 16 and parameters for the same will be described in detail.

[0427] When MIMO (single-layer MIMO) is used, the baseband time domain signal after IFFT can be described in a polarization-specific fashion as shown in Equation 4 below.

[0428] [Mathematical Formula 4]

[0429]

[0430] Ψ in the above mathematical equation 4 l,k (t), Ψ m,l,k (t), k, l, m and c l,k The parameters such as [etc.] have already been explained.

[0431] As described above, a can represent a polarization (antenna) index. In this case, a can be set to 0 for the first polarization and a can be set to 1 for the second polarization.

[0432] As mentioned above, c a,m,l,kcan be the complex modulation value for carrier k of the OFDM symbol number l in subframe number m associated with polarization (antenna) a. That is, c a,m,l,k may be the cell signal value of the k-th subcarrier of the l-th OFDM symbol of the m-th subframe among the signals transmitted in polarization a.

[0433] At this time, S M,a may be the set of subframe numbers, for which polarization a is active during the corresponding transmission. In this case, S M,0 is a first subframe indicator set for the first polarization, and S M,1 may be a second subframe indicator set for second polarization.

[0434] At this time, NoC P,l , NoC m , L SFm , L Fp and N SF The back is as described above.

[0435] At this time, P preamble,l is (l + 1) th The per-polarization frequency domain total power of the preamble symbol (the per-polarization frequency domain total power of (l + 1) th It can represent the preamble symbol.

[0436] At this time, P data,mIt can represent the per-polarization frequency domain total power of each data and subframe boundary symbol in subframe m.

[0437] All other parameters of the above mathematical formula 4 are as previously described, and parameters not explicitly defined here may be used as defined in the existing ATSC 3.0 A / 322 standard.

[0438] In this case, the MIMO transmitter may be required to transmit the same preamble symbol for the first and second polarizations. Therefore, in Equation 4 above, the common value c is independent of the polarization index a. l,k This can be shared. Carrier signals at data and subframe boundary symbols may differ between polarizations, and thus the corresponding carrier modulation value c a,m,l,k Polarization—can be uniquely defined (Carrier signals in data and subframe boundary symbols may differ between polarization, and hence the corresponding carrier modulation value c a,m,l,k may be defined as polarization-specific).

[0439] IFFT power normalization for MIMO can be applied to each polarization stream. For the use of MIMO, P preamble,l and P data,m The definitions of may need to be defined as the total power in the frequency domain per polarization. In this case, P for MIMO preamble,l and P data,mThe evaluation of can be the same as SISO processing.

[0440] The MIMO-version post-IFFT signal representation described in Equation 4 is compatible with the examples of FIGS. 15 and 16 above, and the subframe indicator set S M,a This may vary depending on the embodiment.

[0441] If all subframes within a frame use MIMO, S M,a Regardless of the value of a, 0 ≤ m < N SF (N SF must be composed of all integers within the range of the number of subframes within the above frame. That is, S M,a = {0, ..., N SF - 1} must be.

[0442] TDM of MIMO subframe(s) and SISO subframe(s) may involve the transmission of SISO signals in the MIMO transmitter. In this case, the transmission of SISO signals in the MIMO transmitter may be performed in one of the examples of FIG. 15 and FIG. 16 described above.

[0443] If, during the subframe duration using SISO, only the first polarization is enabled and the second polarization is disabled during that time, S M,a For a which is 0, S M,a = {0, ..., N SF - 1}, and for a which is 1, it must consist of subframe numbers using MIMO. For example, the total N SF = 4 If MIMO is applied to subframes 2 and 3 among the 4 subframes, S M,1 (The second subframe indicator set) is {2, 3}, and S M,0 (The first subframe indicator set) can be {0, 1, 2, 3}.

[0444] If both the first and second polarizations are enabled during the subframe duration using SISO, S M,a Regardless of the value of a, 0 ≤ m < N SF (N SF must be composed of all subframe numbers within the number of subframes within the above frame). That is, S M,a = {0, ..., N SF It must be {- 1}. In this case, c a,m,l,k is when m points to a SISO subframe, c 0,m,l,k = c 1,m,l,k It can be done.

[0445] A broadcast signal frame containing a layered MIMO subframe can be transmitted using a broadcast signal transmitting device illustrated in FIGS. 3 and 5 (Type B, second layered MIMO) or FIGS. 2 and 4 (or FIG. 12) (Type A, first layered MIMO).

[0446] Figures 17 and 18 are diagrams showing examples of broadcast signal frames transmitted through two polarizations when layered MIMO is applied.

[0447] Referring to FIG. 17, it can be seen that a first type layered MIMO is applied, and layered multiplexed streams are transmitted with first and second polarization.

[0448] Referring to FIG. 18, it can be seen that a second type layered MIMO is applied so that a layered multiplexed stream is transmitted to the first polarization, and a single layer stream (enhanced layer) is transmitted to the second polarization.

[0449] FIG. 19 is a diagram showing an example in which two or more of the subframes using SISO, MIMO, and layered MIMO methods are TDMed.

[0450] Referring to FIG. 19, it can be seen that a second type layered MIMO subframe and a MIMO subframe are included in one frame through TDM.

[0451] In the example illustrated in FIG. 19, a case was given in which a second type layered MIMO subframe is positioned before a MIMO subframe, but according to the embodiment, a MIMO subframe may be positioned before a second type layered MIMO subframe. That is, it may be required that a subframe with high transmission power be positioned preferentially within the frame. In this case, the power of the preamble symbol of the second polarization may be set based on the power of the data symbol of the first subframe that activates the second polarization. In this case, the power of the preamble symbol of the second polarization may be set to be equal to the power of the data symbol of the first subframe that activates the second polarization.

[0452] Layered MIMO subframes (Type 1 layered MIMO subframe and Type 2 layered MIMO subframe) can also be TDMed with other subframes (Non-MIMO subframe and MIMO subframe). In such TDM cases, the baseband time domain signal can be described by a polarization-specific expression as shown in Equation 5 below.

[0453] [Mathematical Formula 5]

[0454]

[0455] At this time, S M,a may be the set of subframe numbers, for which polarization a is active during the corresponding transmission. In this case, S M,0 is a first subframe indicator set for the first polarization, and S M,1may be a second subframe indicator set for second polarization.

[0456] The layered MIMO-version post-IFFT signal representation described in Equation 5 can be compatible with the examples of FIGS. 15, 16, 17, 18, 19, 20, and 21, and the subframe indicator set S M,a This may vary depending on the embodiment.

[0457] In this case, if subframe m is not a layered MIMO subframe, K m [a] can be 1. In this case, if the first subframe is not a layered MIMO subframe, K0[a] can be 1.

[0458] At this time, for each polarization, the power of the preamble symbol may refer to the data symbol power of the first subframe activating the corresponding polarization. This is, S M,a (i) This S M,a Scaling factor K when representing the (i+1)th element of SM,a(0) It can be indicated by [a]. That is, S in Equation 5 M,a (0) is S M,a Represents the first element of.

[0459] According to an embodiment, the subframes have a scaling factor K m [1] can be sorted in descending order.

[0460] When a pure SISO subframe is transmitted in a layered MIMO transmitter such as the examples shown in FIGS. 3 and 4 or FIGS. 12 ( FIGS. 2 and 4), the SISO (Non-MIMO) subframe may be transmitted only through polarization 1 while the second polarization is disabled, or the first polarization and the second polarization may transmit identical signal copies of the SISO subframes.

[0461] If SISO (Non-MIMO) subframes are transmitted only through Pollution 1 and Pollution 2 is disabled during that time, S M,0 is 0 ≤ m < N SF It can be composed of all integers. That is, S M,0 is {0, ..., N SF It can be -1}. In this case, S M,1 It can be composed of subframe numbers using MIMO or layered MIMO.

[0462] If the first polarization and the second polarization transmit identical signal copies of SISO subframes, S M,a 0 ≤ m < N regardless of the value of a SF It can be composed of all integers. That is, S M,a is {0, ..., N regardless of the value of a SF It can be -1}. In this case, c a,m,l,k is when m points to a SISO subframe, c 0,m,l,k = c 1,m,l,k It can be done.

[0463] Other parameters are as described above.

[0464] According to an embodiment, all enhanced layer physical layer pipes within a subframe using a second type layered MIMO may be required to use the same injection level.

[0465] That is, K in the aforementioned mathematical formulas 1 and 5 m [a] can be a non-1 value only for the second polarization. In this case, K m [a] is a value determined by the injection level of the enhanced layer.

[0466] The injection level of the enhanced layer can be set independently for each physical layer, but in the above mathematical formulas 1 and 5, K at a unit more granular than the subframe m [a] cannot be set differently.

[0467] Therefore, when Type 2 layered MIMO is applied, all enhanced layer physical layer pipes within the subframe may be required to use the same injection level.

[0468] Furthermore, in order to maintain the uniformity of the transmission structure combining layered division multiplexing and MIMO, not only when Type 2 layered MIMO is applied but also when Type 1 layered MIMO is applied, it may be required that all enhanced layer physical layer pipes within a subframe use the same injection level.

[0469] Ultimately, when layered MIMO is applied, all enhanced layer physical layer pipes within a subframe may be required to use the same injection level.

[0470] FIG. 20 is a diagram showing an example of a broadcast signal frame containing a second type layered MIMO subframe transmitted with two polarizations.

[0471] Referring to FIG. 20, it can be seen that within one second type layered MIMO subframe (SUBFRAME 0), the injection levels of the layered multiplexed enhanced layer physical layer pipes (PLP2, PLP3) are maintained at the same level.

[0472] FIG. 21 is a diagram showing an example of a broadcast signal frame containing a first type layered MIMO subframe transmitted with two polarizations.

[0473] Referring to FIG. 21, it can be seen that within one first type layered MIMO subframe (SUBFRAME 0), the injection levels of the layered multiplexed enhanced layer physical layer pipes (PLP2, PLP3) are maintained at the same level.

[0474] The first type layered MIMO shown in FIGS. 2 and 4 and the second type layered MIMO shown in FIGS. 3 and 5 can be signaled by the first 1-bit field and the second 1-bit field as described above.

[0475] At this time, the first 1-bit field may be L1B_first_sub_mimo (for the first subframe) or L1D_mimo (for other subframes), and the second 1-bit field may be L1B_first_sub_mimo_mixed (for the first subframe) or L1D_mimo_mixed (for other subframes).

[0476] That is, the first type layered MIMO and the second type layered MIMO can be distinguished by a combination (conjunction) of a first 1-bit field such as L1B_first_sub_mimo (for the first subframe) or L1D_mimo (for other subframes) and a first 1-bit field such as L1B_first_sub_mimo_mixed (for the first subframe) or L1D_mimo_mixed (for other subframes).

[0477] As mentioned above, L1B_first_sub_mimo and L1D_mimo are fields that indicate whether MIMO is applied to the corresponding subframe, and can indicate whether MIMO is applied to all physical layer pipes of the corresponding subframe.

[0478] That is, L1B_first_sub_mimo is set to 1 if MIMO processing is applied to all physical layer pipes of the first subframe, and can be set to 0 if at least one physical layer pipe that is not MIMO processed is included in the first subframe. In this case, L1B_first_sub_mimo is set to 1 if MIMO is applied to all core layer physical layer pipes within the first subframe of the current frame, and can be set to 0 otherwise.

[0479] Additionally, L1D_mimo can be set to 1 if MIMO processing is applied to all physical layer pipes in the current subframe, and to 0 if at least one physical layer pipe that is not MIMO processed is included in the current subframe. In this case, L1D_mimo can be set to 1 if MIMO is applied to all core layer physical layer pipes within the current subframe from the second onwards of the given frame, and to 0 otherwise.

[0480] As mentioned above, when Type 2 layered MIMO is applied, MIMO is not applied to the core layer physical layer pipe, so L1B_first_sub_mimo or L1D_mimo can be set to 0 instead of 1.

[0481] L1B_first_sub_mimo_mixed can be included in L1-Basic parameters, just like L1B_first_sub_mimo. In this case, L1B_first_sub_mimo_mixed can indicate whether the first subframe of the current frame multiplexes physical layer pipes that use MIMO with other physical layer pipes that do not use MIMO. That is, if physical layer pipes that use MIMO and physical layer pipes that do not use MIMO are multiplexed in the first subframe, L1B_first_sub_mimo_mixed can be set to 1. If all physical layer pipes within the first subframe use MIMO (L1B_first_sub_mimo = 1) or do not use MIMO (L1B_first_sub_mimo = 0), L1B_first_sub_mimo_mixed can be set to 0.

[0482] In this case, L1B_first_sub_mimo_ldm may be used as the second 1-bit field. L1B_first_sub_mimo_ldm may indicate whether MIMO is used for the enhanced layer in the first subframe of the current frame, subject to the use of SISO in the associated core layer. If L1B_first_sub_mimo_ldm is set to 1, it may indicate that MIMO is used only in the given enhanced layer and not in the core layer, and that LDM is used in the first subframe. L1B_first_sub_mimo_ldm may be set to 0 in cases where MIMO is used or not used in both the core layer and the enhanced layer, or where LDM is not used in the first subframe.

[0483] Table 5 below shows the L1-Basic signaling fields and syntax including L1B_first_sub_mimo_mixed.

[0484] SyntaxNo. of BitsFormatL1_Basic_signaling() {L1B_version3uimsbfL1B_mimo_scattered_pilot_encoding1uimsbfL1B_lls_flag1uimsbfL1B_time_info_flag2uimsbfL1B_return_channel_flag1uimsbfL1B_papr_reduction2uimsbfL1B_frame_length_mode1uimsbfif (L1B_frame_length_mode=0 ) {L1B_frame_length10uimsbfL1B_excess_samples_per_symbol13uimsbf} else{L1B_time_offset16uimsbfL1B_additional_samples7uimsbf}L1B_num_subframes8uimsbfL1B_preamble_num_symbols3uimsbfL1B_preamble_reduced_carriers3uimsbfL1B_L1_Detail_content_tag2uimsbfL 1B_L1_Detail_size_bytes13uimsbfL1B_L1_Detail_fec_type3uimsbfL1B_L1_Detail_additional_parity_mode2uimsbfL1B_L1_Detail_total_cells19uimsbfL1B_first_sub_mimo1uimsbfL1B_first_sub_miso 2uimsbfL1B_first_sub_fft_size2uimsbfL1B_first_sub_reduced_carriers3uimsbfL1B_first_sub_guard_interval4uimsbfL1B_first_sub_num_ofdm_symbols11uimsbfL1B_first_sub_scattered_pilot_pat tern5uimsbfL1B_first_sub_scattered_pilot_boost3uimsbfL1B_first_sub_sbs_first1uimsbfL1B_first_sub_sbs_last1uimsbfL1B_first_sub_mimo_mixed1uimsbfL1B_reserved47uimsbfL1B_crc32uimsbf}

[0485] L1B_first_sub_mimo_mixed may be replaced by L1B_first_sub_mimo_mixed instead of L1B_first_sub_mimo_ldm.

[0486] Table 6 below shows the channel format for L1B_first_sub_mimo_mixed with L1B_first_sub_mimo.

[0487] MIMO ConfigurationsRelated L1-Basic Signaling AssignmentL1B_first_sub_mimoL1B_first_sub_mimo_mixedAll PLPs in first subframe use SISO00PLPs of both types in first subframe01All PLPs in first subframe use MIMO10Invalid Combination11

[0488] As can be seen from Table 6, setting L1B_first_sub_mimo to 1 can be mutually exclusive with setting L1B_first_sub_mimo_mixed to 1.

[0489] When LDM is applied to the first subframe of a frame, L1B_first_sub_mimo_mixed set to 1 may indicate that MIMO processing is applied to all enhanced layer physical layer pipes of this subframe, and MIMO processing is not applied to all core layer physical layer pipes.

[0490] If all physical layer pipes of the first subframe are SISO or MIMO, any of the available multiplexing schemes (TDM, FDM, LDM, and combinations thereof) can be applied.

[0491] In this case, if MIMO needs to be applied differently depending on the layer within a subframe, LDM multiplexing must be applied to that subframe. In this case, TDM, FDM, or a combination thereof may be applied to each layer or both layers as needed.

[0492] When physical layer pipe(s) (enhanced layer physical layer pipe(s)) with L1D_plp_layer > 0 exist in the first subframe of the current frame, the type of layered MIMO can be signaled by L1B_first_sub_mimo_mixed in conjunction with L1B_first_sub_mimo. The first type of layered MIMO can be signaled by two parameters L1B_first_sub_mimo_mixed = 0 and L1B_first_sub_mimo = 1, and the second type of layered MIMO can be signaled by two parameters L1B_first_sub_mimo_mixed = 1 and L1B_first_sub_mimo = 0.

[0493] By signaling the layered MIMO type with a combination of the two signaling fields in this way, the layered MIMO type can be signaled efficiently while ensuring compatibility with existing receivers.

[0494] L1D_mimo_mixed can be included in L1-Detail subframe parameters, just like L1D_mimo. In this case, L1D_mimo_mixed can indicate whether the current subframe multiplexes physical layer pipes that use MIMO with other physical layer pipes that do not use MIMO. That is, if physical layer pipes that use MIMO and physical layer pipes that do not use MIMO are multiplexed in the current subframe, L1D_mimo_mixed can be set to 1. If all physical layer pipes in the current subframe use MIMO (L1D_mimo = 1) or do not use MIMO (L1D_mimo = 0), L1D_mimo_mixed can be set to 0.

[0495] In this case, L1D_mimo_ldm may be used as the second 1-bit field. L1D_mimo_ldm may indicate whether MIMO is used for the enhanced layer in the current subframe, subject to the use of SISO in the associated core layer. If L1D_mimo_ldm is set to 1, it may indicate that MIMO is used only in the given enhanced layer and not in the core layer, and that LDM is used in the current subframe. L1D_mimo_ldm may be set to 0 in cases where MIMO is used or not used in both the core layer and the enhanced layer, or where LDM is not used in the current subframe.

[0496] Table 7 below shows the L1-Detail signaling fields and syntax including L1D_mimo_mixed.

[0497] SyntaxNo. of BitsFormatL1_Detail_signaling() {L1D_version4UimsbfL1D_num_rf3Uimsbffor (L1D_rf_id=1 .. L1D_num_rf){L1D_bonded_bsid16Uimsbfreserved3Bslbf}if (L1B_time_info_flag!= 00) {L1D_time_sec32UimsbfL1D_time_msec10Uimsbfif (L1B_time_info_flag!= 01) {L1D_time_usec10Uimsbfif (L1B_time_info_flag!= 10) {L1D_time_nsec10Uimsbf}}}for (i=0 .. L1B_num_subframes) {if (i > 0) {L1D_mimo1UimsbfL1D_miso2UimsbfL1D_fft_size2UimsbfL1D_reduced_carriers3UimsbfL1D_guard_interval4UimsbfL1D_num_ofdm_symbols11UimsbfL1D_scattered_pilot_pattern5UimsbfL1D_scattered_pilot_boost3UimsbfL1D_sbs_first1UimsbfL1D_sbs_last1Uimsbf}if (L1B_num_subframes>0) {L1D_subframe_multiplex1Uimsbf}L1D_frequency_interleaver1Uimsbfif (((i=0)&&(L1B_first_sub_sbs_first || L1B_first_sub_sbs_last)) ||((i>0)&&(L1D_sbs_first | L1D_sbs_last))) {L1D_sbs_null_cells13Uimsbf}L1D_num_plp6Uimsbffor (j=0 ..L1D_num_plp) {L1D_plp_id6UimsbfL1D_plp_lls_flag1UimsbfL1D_plp_layer2UimsbfL1D_plp_start24UimsbfL1D_plp_size24UimsbfL1D_plp_scrambler_type2UimsbfL1D_plp_fec_type4Uimsbfif (L1D_plp_fec_type∈{0,1,2,3,4,5}) {L1D_plp_mod4UimsbfL1D_plp_cod4Uimsbf}L1D_plp_TI_mode2Uimsbfif (L1D_plp_TI_mode=00) {L1D_plp_fec_block_start15Uimsbf} else if (L1D_plp_TI_mode=01) {L1D_plp_CTI_fec_block_start22Uimsbf}if (L1D_num_rf>0) {L1D_plp_num_channel_bonded3Uimsbfif (L1D_plp_num_channel_bonded>0) {L1D_plp_channel_bonding_format2Uimsbffor (k=0..L1D_plp_num_channel_bonded){L1D_plp_bonded_rf_id3Uimsbf}}}if (i=0 &&L1B_first_sub_mimo=1) || (i >0 &&L1D_mimo=1) {L1D_plp_mimo_stream_combining1UimsbfL1D_plp_mimo_IQ_interleaving1UimsbfL1D_plp_mimo_PH1Uimsbf}if (L1D_plp_layer=0) {L1D_plp_type1Uimsbfif (L1D_plp_type=1) {L1D_plp_num_subslices14UimsbfL1D_plp_subslice_interval24Uimsbf}if (((L1D_plp_TI_mode=01) ||(L1D_plp_TI_mode=10))&&(L1D_plp_mod=0000)) {L1D_plp_TI_extended_interleaving1Uimsbf}if (L1D_plp_TI_mode=01) {L1D_plp_CTI_depth3UimsbfL1D_plp_CTI_start_row11Uimsbf}else if (L1D_plp_TI_mode=10) {L1D_plp_HTI_inter_subframe1UimsbfL1D_plp_HTI_num_ti_blocks4UimsbfL1D_plp_HTI_num_fec_blocks_max12Uimsbfif (L1D_plp_HTI_inter_subframe=0) {L1D_plp_HTI_num_fec_blocks12Uimsbf}else {for (k=0..L1D_plp_HTI_num_ti_blocks) {L1D_plp_HTI_num_fec_blocks12Uimsbf}}L1D_plp_HTI_cell_interleaver1Uimsbf}}else {L1D_plp_ldm_injection_level5Uimsbf}}}L1D_bsid16Uimsbffor (i=0 ..L1B_num_subframes) {if (i > 0) {L1D_mimo_mixed1Uimsbf}if (i=0 &&L1B_first_sub_mimo_mixed=1) || (i>0 &&L1D_mimo_mixed=1) {for (j=0 ..L1D_num_plp) {L1D_plp_mimo1Uimsbfif (L1D_plp_mimo=1) {L1D_plp_mimo_stream_combining1UimsbfL1D_plp_mimo_IQ_interleaving1UimsbfL1D_plp_mimo_PH1Uimsbf}}}}L1D_reservedas neededL1D_crc32}.

[0498] In Table 7 above, L1D_mimo_ldm may be included instead of L1D_mimo_mixed in the place of L1D_mimo_mixed.

[0499] The type of layered MIMO may be either a first type layered MIMO or a second type layered MIMO, and this may be determined by the combination (conjunction) of a first 1-bit field (L1B_first_sub_mimo or L1D_mimo) and a second 1-bit field (L1B_first_sub_mimo_mixed or L1D_mimo_mixed).

[0500] In this case, if L1B_first_sub_mimo_mixed = 0 and L1B_first_sub_mimo = 1 for the first subframe, it may mean Type 1 layered MIMO.

[0501] In this case, if L1B_first_sub_mimo_mixed = 1 and L1B_first_sub_mimo = 0 for the first subframe, it may mean Type 2 layered MIMO.

[0502] In this case, for the second and subsequent subframes, if L1D_mimo_mixed = 0 and L1D_mimo = 1, it may mean the first type layered MIMO.

[0503] In this case, if L1D_mimo_mixed = 1 and L1D_mimo = 0 for the second and subsequent subframes, it may mean Type 2 layered MIMO.

[0504] As mentioned above, L1B_first_sub_mimo_ldm can be used instead of L1B_first_sub_mimo_mixed, and L1D_mimo_ldm can be used instead of L1D_mimo_mixed.

[0505] In Table 7 above, L1D_plp_mimo is a 1-bit field that can indicate whether MIMO is used for a given physical layer pipe when the current subframe contains both a physical layer pipe with MIMO applied and a physical layer pipe without MIMO applied.

[0506] At this time, for the second type layered MIMO, precoding parameters (L1D_plp_mimo_stream_combining, L1D_plp_mimo_IQ_interleaving, L1D_plp_mimo_PH) can be defined within a conditional statement corresponding to the second 1-bit field (L1B_first_sub_mimo_mixed or L1D_mimo_mixed).

[0507] Table 8 below shows the signaling format for L1D_mimo_mixed combined with L1D_mimo.

[0508] MIMO ConfigurationsRelated L1-Detail Signaling AssignmentL1D_mimoL1D_mimo_mixedAll PLPs in subframe use SISO00PLPs of both types in subframe01All PLPs in subframe use MIMO10Invalid Combination11

[0509] As can be seen from Table 8, setting L1D_mimo to 1 can be mutually exclusive with setting L1D_mimo_mixed to 1.

[0510] When LDM is applied to the subframe, L1D_mimo_mixed set to 1 may indicate that MIMO processing is applied to all enhanced layer physical layer pipes of this subframe, and MIMO processing is not applied to all core layer physical layer pipes.

[0511] If all physical layer pipes of the corresponding subframe are SISO or MIMO, any of the available multiplexing schemes (TDM, FDM, LDM, and combinations thereof) may be applied.

[0512] In this case, if MIMO needs to be applied differently depending on the layer within a subframe, LDM multiplexing must be applied to that subframe. In this case, TDM, FDM, or a combination thereof may be applied to each layer or both layers as needed.

[0513] When physical layer pipe(s) (enhanced layer physical layer pipe(s)) with L1D_plp_layer > 0 exist in the second and subsequent subframes, the type of layered MIMO can be signaled by L1D_mimo_mixed in conjunction with L1D_mimo. The first type of layered MIMO can be signaled by two parameters L1D_mimo_mixed = 0 and L1D_mimo = 1, and the second type of layered MIMO can be signaled by two parameters L1D_mimo_mixed = 1 and L1D_mimo = 0.

[0514] By signaling the layered MIMO type with a combination of the two signaling fields in this way, the layered MIMO type can be signaled efficiently while ensuring compatibility with existing receivers.

[0515] FIG. 22 is an operation flowchart illustrating a broadcast signal transmission method according to an embodiment of the present invention.

[0516] Referring to FIG. 22, a broadcast signal transmitting device according to one embodiment of the present invention generates at least one core layer signal corresponding to a core layer (S2210).

[0517] In addition, a broadcast signal transmission device according to one embodiment of the present invention generates enhanced layer MIMO (Multiple Input Multiple Output) signals corresponding to the enhanced layer (S2220).

[0518] In addition, a broadcast signal transmission device according to one embodiment of the present invention performs layer division multiplexing corresponding to the core layer and the enhanced layer to output a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization (S2230).

[0519] In addition, a broadcast signal transmission device according to one embodiment of the present invention generates a first polarization transmission signal using the first polarization signal and generates a second polarization transmission signal using the second polarization signal (S2240).

[0520] At this time, at least one of the first polarization transmission signal and the second polarization transmission signal includes a preamble, and the preamble may include a plurality of signaling fields for identifying the type of layered MIMO.

[0521] At this time, the type of the layered MIMO may be either a first type layered MIMO in which MIMO is applied to both the core layer and the enhanced layer, or a second type layered MIMO in which MIMO is applied only to the enhanced layer.

[0522] At this time, if the type of the layered MIMO is the first type layered MIMO, the at least one core layer signal is a core layer MIMO (Multiple Input Multiple Output) signal, the first polarization signal is generated by hierarchically dividing multiplexing one of the core layer MIMO signals and one of the enhanced layer MIMO signals, and the second polarization signal can be generated by hierarchically dividing multiplexing another of the core layer MIMO signals and another of the enhanced layer MIMO signals.

[0523] At this time, if the type of the layered MIMO is the second type layered MIMO, the first polarization signal is generated by layering multiplexing at least one core layer signal and one of the enhanced layer MIMO signals, and the other of the enhanced layer MIMO signals can be output as the second polarization signal.

[0524] At this time, the plurality of signaling fields may be a first 1-bit field that is set to 0 when the subframe includes a physical layer pipe to which MIMO processing is not applied, and a second 1-bit field that is set to 1 when LDM is applied to the subframe and MIMO is used only in the enhanced layer and not in the core layer.

[0525] At this time, the type of layered MIMO can be signaled by using the first 1-bit field and the second 1-bit field together (signaled by the second 1-bit field in conjunction with the first 1-bit field).

[0526] At this time, when layered division multiplexing is applied to a subframe, the first 1-bit field may be set to 1 and the second 1-bit field may be set to 0 to represent the first type layered MIMO, and the first 1-bit field may be set to 0 and the second 1-bit field may be set to 1 to represent the second type layered MIMO.

[0527] At this time, the setting of the second 1-bit field to 1 may be mutually exclusive with the setting of the first 1-bit field to 1.

[0528] At this time, the first type layered MIMO corresponds to all physical layer pipes within the subframe using MIMO, and the second type layered MIMO may correspond to at least one SISO physical layer pipe and at least one MIMO physical layer pipe existing together in the subframe.

[0529] FIG. 23 is an operation flowchart illustrating a method for receiving a broadcast signal according to an embodiment of the present invention.

[0530] Referring to FIG. 23, a method for receiving a broadcast signal according to an embodiment of the present invention receives a broadcast signal including a preamble (S2310).

[0531] At this time, the broadcast signal may correspond to at least one core layer signal corresponding to the core layer and enhanced layer MIMO (Multiple Input Multiple Output) signals corresponding to the enhanced layer.

[0532] At this time, the broadcast signal may be a first polarization signal corresponding to the first polarization and a second polarization signal corresponding to the second polarization.

[0533] In addition, a broadcast signal reception method according to one embodiment of the present invention restores a plurality of signaling fields for identifying the type of layered MIMO included in the preamble (S2320).

[0534] At this time, the type of the layered MIMO may be either a first type layered MIMO in which MIMO is applied to both the core layer and the enhanced layer, or a second type layered MIMO in which MIMO is applied only to the enhanced layer.

[0535] At this time, the plurality of signaling fields may be a first 1-bit field that is set to 0 when the subframe includes a physical layer pipe to which MIMO processing is not applied, and a second 1-bit field that is set to 1 when LDM is applied to the subframe and MIMO is used only in the enhanced layer and not in the core layer.

[0536] At this time, the type of layered MIMO can be signaled by using the first 1-bit field and the second 1-bit field together (signaled by the second 1-bit field in conjunction with the first 1-bit field).

[0537] At this time, when layered division multiplexing is applied to a subframe, the first 1-bit field may be set to 1 and the second 1-bit field may be set to 0 to represent the first type layered MIMO, and the first 1-bit field may be set to 0 and the second 1-bit field may be set to 1 to represent the second type layered MIMO.

[0538] At this time, the setting of the second 1-bit field to 1 may be mutually exclusive with the setting of the first 1-bit field to 1.

[0539] At this time, the first type layered MIMO corresponds to all physical layer pipes within the subframe using MIMO, and the second type layered MIMO may correspond to at least one SISO physical layer pipe and at least one MIMO physical layer pipe existing together in the subframe.

[0540] At this time, if the type of the layered MIMO is the first type layered MIMO, the at least one core layer signal is a core layer MIMO (Multiple Input Multiple Output) signal, the first polarization signal is generated by hierarchically dividing multiplexing one of the core layer MIMO signals and one of the enhanced layer MIMO signals, and the second polarization signal can be generated by hierarchically dividing multiplexing another of the core layer MIMO signals and another of the enhanced layer MIMO signals.

[0541] At this time, if the type of the layered MIMO is the second type layered MIMO, the first polarization signal is generated by layering multiplexing at least one core layer signal and one of the enhanced layer MIMO signals, and the other of the enhanced layer MIMO signals can be output as the second polarization signal.

[0542] In addition, a broadcast signal reception method according to one embodiment of the present invention restores data based on the signaling fields (S2330).

[0543] At this time, when the first polarization transmission signal and the second polarization transmission signal generated through the transmission structure of FIGS. 3 and FIGS. 5 are received, the core layer stream can be restored through decoding corresponding to the first polarization.

[0544] At this time, when the first polarization transmission signal and the second polarization transmission signal generated through the transmission structure of FIGS. 2 and FIGS. 4 are received, the core layer stream can be restored through MIMO decoding corresponding to the first polarization and the second polarization.

[0545] Each step illustrated in FIGS. 22 and FIGS. 23 may be performed in the order illustrated in FIGS. 22 and FIGS. 23, in reverse order, or simultaneously.

[0546] FIG. 24 is a block diagram showing the configuration of a computer system according to an embodiment of the present invention.

[0547] The broadcast signal transmitting device, the broadcast signal receiving device, and the individual components constituting these devices according to the embodiment can be implemented in a computer system (2400).

[0548] A computer system (2400) may include one or more processors (2410), memory (2430), user interface input device (2440), user interface output device (2450), and storage (2460) that communicate with each other via a bus (2420). Additionally, the computer system (2400) may further include a network interface (2470) connected to a network (2480). The processor (2410) may be a semiconductor device that executes programs or processing instructions stored in a central processing unit or memory (2430) or storage (2460). The memory (2430) and storage (2460) may be storage media comprising at least one of a volatile medium, a non-volatile medium, a removable medium, a non-removable medium, a communication medium, or an information transfer medium. For example, the memory (2430) may include a ROM (2431) or a RAM (2432).

[0549] At this time, at least one program can be written to the memory (2430).

[0550] At this time, the processor (2410) can execute the program. At this time, the program can perform each step shown in FIG. 22 or each step shown in FIG. 23.

[0551] FIG. 25 is a block diagram showing an example of a device for estimating the performance of a MIMO system according to an embodiment of the present invention.

[0552] Referring to FIG. 25, a device for estimating the performance of a MIMO system according to an embodiment of the present invention includes an input processing unit (2510), a MIMO required performance estimation unit (2520), and an output interface unit (2530).

[0553] The input processing unit (2510) generates input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information.

[0554] In this case, the SISO required performance may correspond to the SISO ToV (Threshold of Visibility). For example, the SISO required performance may be the required C / N (Signal-to-Noise Ratio) estimate of the SISO system. For example, the SISO required performance is the τ to be described later. SISO It could be.

[0555] In this case, the cross-channel discrimination information may be Cross-Polarization Discrimination (XPD). In this case, the XPD may be the channel XPD described later.

[0556] At this time, channel condition information may be a parameter that identifies a channel model condition. For example, channel condition information may be ChMod, which will be described later, and may represent one of the AWGN, RL, or RC channels.

[0557] In the example illustrated in FIG. 25, the input processing unit (2510) includes the SISO transmission ToV of the ModCod combination of interest (required C / N of the SISO system), estimated class information (whether it is Class P or Class E, to be described later), LDM information, channel model information, and Line-of-Sight (LoS) component XPD (XPD L ), NLoS (Non-LoS) component XPD (XPD N The above input information can be generated by receiving ), pilot boosting information, pilot pattern information, etc. In this case, the channel model information may correspond to channel condition information and may correspond to ChMod described later. In this case, the pilot boosting information is F, which represents the dB scale power of pilot boosting applied to scattered pilots. PB It may be. In this case, the pilot pattern information may be pilot separation information, and D to be described later x and D y It may include one or more of the following. In this case, the LDM information may include whether LDM is applied, information on the layer to be estimated within the LDM, the Injection Level (IL), etc.

[0558] In the example illustrated in Fig. 25, LDM IL represents the injection level of LDM, PILOT BOOSTING represents pilot boosting information, and MP PATTERN represents pilot pattern information.

[0559] The MIMO required performance estimation unit (2520) generates MIMO required performance from the SISO required performance using the channel condition information and cross-channel distinction information.

[0560] At this time, the MIMO required performance can be generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the channel condition information and the cross-channel distinction information.

[0561] At this time, the correction input value is input into a correction offset function, and the output of the correction offset function can correspond to the MIMO required performance.

[0562] At this time, the correction offset function may vary depending on the channel condition information (e.g., ChMod described later).

[0563] At this time, the correction offset function may vary depending on the cross-channel distinction information.

[0564] At this time, the MIMO system is a first type layered MIMO system, and the MIMO required performance may include one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer.

[0565] At this time, the core layer MIMO required performance and the enhanced layer MIMO required performance can be generated based on the injection level.

[0566] At this time, the MIMO required performance can be estimated using either a first mode (Class P) corresponding to error-free complete channel estimation or a second mode (Class E) corresponding to error-prone channel estimation.

[0567] At this time, the input information may further include pilot boosting information and pilot separation information in the second mode. At this time, the pilot boosting information is F to be described later. PBIt may be, and the pilot interval information will be described later D x and D y It may include.

[0568] At this time, the MIMO required performance estimation unit may include a Class P estimation unit (2527) and a Class E estimation unit (2528).

[0569] At this time, the Class P estimation unit (2527) can perform the Class P estimation described later, and the Class E estimation unit (2528) can perform the Class E estimation described later.

[0570] As will be explained later, Class P corresponds to the case where complete CSI is assumed, and Class E may correspond to the case where channel estimation errors exist.

[0571] In the example illustrated in FIG. 25, the class P estimation unit (2527) includes a transmission mode-specific calculator (2521) and a detailed correction offset model (2522), and the class E estimation unit (2528) includes a transmission mode-specific calculator (2523) and a detailed correction offset model (2524). At this time, the components included in the class P estimation unit (2527) and the class E estimation unit (2528) may be shared or provided separately.

[0572] The detailed correction offset model (2522, 2524) illustrated in FIG. 25 can generate a correction offset based on channel condition information (e.g., ChMod) and provide it to a transmission mode-specific calculator (2521, 2523).

[0573] The transmission mode-specific calculator (2521, 2523) illustrated in FIG. 25 can generate MIMO required performance from SISO required performance using a correction offset. At this time, the transmission mode-specific calculator (2523) may include a channel estimation effect extraction unit.

[0574] The output interface unit (2530) generates a system output based on the MIMO required performance.

[0575] For example, the output interface unit (2530) can output the MIMO required performance as is to the system output. That is, the output of the output interface unit (2530) may be an estimate of the MIMO required performance.

[0576] For example, the output interface unit (2530) may generate a coverage output based on the result of comparing the MIMO required performance and the comparison target performance corresponding to a specific location, and may output this coverage output as a system output. For example, the device provided by an embodiment of the present invention may estimate coverage based on the required signal quality of the estimated MIMO system or the first type layered MIMO system and plot the estimated coverage on a map. At this time, coverage may be estimated through a comparison between the required signal quality of the corresponding point and the received signal quality measurement or prediction. At this time, if the required signal quality is the required CNR, an area including points having a CNR measurement or CNR prediction higher than the required CNR may be plotted as the area covered by the corresponding MIMO broadcast signal.

[0577] In this way, when the output interface unit (2530) outputs a coverage output, the device illustrated in FIG. 25 can be seen as a device for estimating the coverage of a MIMO system.

[0578] An apparatus for estimating the performance of a MIMO system or an apparatus for estimating the coverage of a MIMO system according to one embodiment of the present invention may be implemented based on a computer system illustrated in FIG. 24.

[0579] That is, the device for estimating the performance of a MIMO system, the device for estimating the coverage of a MIMO system, and the individual components constituting these devices according to an embodiment of the present invention may be implemented in a computer system (2400) illustrated in FIG. 24. At this time, the program executed by the processor (2410) illustrated in FIG. 24 may perform each step illustrated in FIG. 27 or each step illustrated in FIG. 28, which will be described later.

[0580] The cross-polarization MIMO method of the ATSC 3.0 broadcasting system utilizes two orthogonal polarized waves to secure two independent transmission paths within the same frequency. However, in actual systems, mutual interference between polarized signals may occur. For example, a signal that should be transmitted in vertical polarization may be partially mixed in with horizontal polarization. This phenomenon does not occur only during transmission; a signal transmitted in vertical polarization may also be partially converted to horizontal polarization as it passes through the propagation path. Mutual interference between polarized signals can be attributed to the following two main factors.

[0581] - Signal ingress between polarizations of transmitted waves due to limitations in transmitting antenna element performance / Signal ingress between polarizations of received waves due to limitations in receiving antenna element performance

[0582] - Polarization conversion occurring from reflections in the propagation path

[0583] Cross-Polarization Discrimination (XPD) is used as an indicator to quantify the mixing of polarized signals resulting from this, and it refers to the following ratio based on the input and output signals for a specific signal action block (e.g., channel, antenna).

[0584] [Mathematical Formula 6]

[0585] (Magnitude of Co-Polarization signal) / (Magnitude of Cross-Polarization signal)

[0586] At this time, the Co-Polarization signal of the above mathematical formula 6 may be a signal in which polarization is maintained during the input / output process, and the Cross-Polarization signal may be a signal in which polarization is switched to the opposite side during the input / output process.

[0587] According to the embodiment, the ratio of the above mathematical formula 6 may be a ratio of signal power rather than a ratio of signal magnitude.

[0588] In other words, it can be seen that the larger the XPD, the less mixing there is between polarized signals, and the smaller the XPD, the more mixing there is between polarized signals.

[0589] Here, the XPD described from the perspective of the entire channel undergone by the modulated signal, encompassing the antenna and the transmission path, can be referred to as Channel XPD. Additionally, the XPD described from the perspective of polarization mixing caused by the component characteristics of the transmitting and receiving antennas, respectively, can be referred to as Antenna XPD. Antenna XPD can be classified according to the performance specifications of the antenna components. Furthermore, Channel XPD can be influenced by Antenna XPD.

[0590] Generally, XPD described from the perspective of the overall system may correspond to channel XPD. On the other hand, XPD described from the perspective of antenna characteristics and performance may correspond to antenna XPD.

[0591] The following two techniques related to XPD are presented.

[0592] - A method for estimating MIMO system performance under a corresponding channel XPD from previously measured SISO system performance using channel XPD values.

[0593] - In relation to the above, a method for calculating channel XPD from antenna XPD and environmental characteristic values

[0594] In this case, Cross-Polarization Discrimination (XPD) may be a sub-concept of Cross-Channel Discrimination. For example, Cross-Channel Discrimination may be an indicator that quantifies the mixing between two non-polarized antenna signals. In this case, the channels may be channels between multiple transmitting antennas and multiple receiving antennas used in MIMO.

[0595] Designing and configuring a wireless transmission network requires information regarding the required quality of the received radio signal, such as the received power, Signal-to-Noise Ratio (SNR), or Carrier-to-Noise Ratio (CNR).

[0596] The coverage of the transmission network is estimated by comparing the required signal quality with the predicted received signal quality at each receiving location, and based on this, network designers / operators can determine or adjust the location of transmitters, transmission power, and antenna placement.

[0597] For example, the device provided by an embodiment of the present invention can estimate coverage based on the required signal quality of an estimated MIMO system or a first type layered MIMO system and plot the estimated coverage on a map. In this case, coverage can be estimated through a comparison between the required signal quality of a corresponding point and a measured or predicted value of the received signal quality. In this case, if the required signal quality is the required CNR, an area including points having a CNR measured value or CNR predicted value higher than the required CNR can be plotted as the area covered by the MIMO broadcast signal.

[0598] Commonly used information may include the required SNR, required CNR, and minimum receiver field strength, and in OFDM systems, this may vary depending on a combination of modulation constellations, channel coding, and multiplexing schemes.

[0599] In this case, the required SNR, required CNR, and minimum received field may vary depending on the channel fading pattern and reception technique, but quantified values ​​(or ranges of values) under a categorized channel fading model and the assumption of a standard reference receiver may be used.

[0600] ATSC 3.0 defines over 100 Modulation Constellation-Channel Coding (ModCod) combinations, and Document A / 327 of the ATSC 3.0 standard provides reference required CNR measurements for each ModCod combination, limited to single-layer SISO transmissions, to aid network operators in network design and operation. For example, Table A.3.2 of Document A / 327 specifies BER = 10 after Low Density Parity Check (LDPC) and Bose-Chaudhuri-Hocquenghem (BCH) decoding under an AWGN channel. -6 The required CNR for each modulation constellation-channel coding (ModCod) combination is listed in dB units.

[0601] For SISO transmission using Layered Division Multiplexing (LDM), the required CNR of the core layer and the enhanced layer can be calculated by utilizing the required CNR threshold of single-layer SISO transmission.

[0602] MIMO or layered MIMO can use the same modulation constellation-channel coding (ModCod) combinations as SISO, but the reception performance may differ from that of SISO.

[0603] This is because mutual influence occurs between polarized signals on the transmitting and receiving antennas and channel propagation, and also because the receiver additionally operates a MIMO equalization module to equalize the two polarized channels.

[0604] Obtaining a list of required CNR measurements for MIMO broadcast signals for each physical layer configuration requires repeating the entire process performed in SISO transmission for each channel XPD value under consideration, and the task itself is more complex. Therefore, obtaining required CNR thresholds for MIMO and layered MIMO entails practical difficulties.

[0605] Therefore, obtaining the required performance for MIMO or layered MIMO from the required performance (required CNR, etc.) for SISO that has already been secured can be a very efficient means to efficiently estimate the reception coverage of a MIMO or layered MIMO transmission network and for network designers or network operators to determine or adjust the location of transmitters, transmission power, and antenna placement.

[0606] According to an embodiment of the present invention, a technique is presented for estimating the required CNR under MIMO and first-type layered MIMO transmission by recycling previously measured required CNR data under SISO transmission.

[0607] That is, if the CNR required under SISO transmission for a specific modulation constellation-channel coding (ModCod) combination is known, an estimate of the CNR required when MIMO or first-type layered MIMO transmission applies the same modulation constellation-channel coding (ModCod) combination can be calculated.

[0608] At this time, the following two estimation methods (estimation modes) may be used, and the criterion for distinguishing these two methods may be whether there is an error in the channel information acquired by the receiver.

[0609] - Class P: When the receiver acquires ideal, error-free channel information (Perfect CSI (Channel State Information)).

[0610] - Class E: When the receiver actually performs channel estimation to obtain channel estimation information

[0611] One embodiment of the present invention may provide an estimation method for AWGN, Rayleigh, and Rician channel model conditions, and may provide an estimation method for channel XPD combinations as described in Table 10 below.

[0612] One embodiment of the present invention can provide a method for estimating a required CNR that simultaneously considers the effect of pilot boosting on channel estimation quality and the effect on the reduction of data signal power.

[0613] One embodiment of the present invention may provide a method for estimating a channel XPD using input information on the antenna XPD, which is the element performance of a transmitting and receiving antenna, and the rate of change in polarization due to reflection on the propagation path. Through this, a channel XPD assigned to a MIMO or first-type layered MIMO transmission system can be obtained from the specifications of the installed transmitting and receiving antennas and environmental conditions.

[0614] One embodiment of the present invention can be used as a key element for driving a coverage calculator for polarized multiplexed MIMO transmission and can be applied to transceivers and other products.

[0615] First, the method for estimating the required CNR of MIMO and Type 1 layered MIMO will be explained in detail.

[0616] Below, we describe a tractable measure for predicting the physical layer performance of an ATSC 3.0 MIMO system. By referring to previously evaluated measurements for an ATSC 3.0 SISO system, the performance of the SISO system can be mapped to the performance of the MIMO system.

[0617] The estimation according to one embodiment of the present invention can capture performance degradation caused by cross-polarization interference occurring in the MIMO channel.

[0618] The required CNR (C / N) increase is identified as dependent on XPD, and when an XPD value is given as part of the channel conditions, the estimation according to one embodiment of the present invention can convert the required C / N data for SISO into a performance estimate for a MIMO system using the same ModCod combination.

[0619] In this case, system performance may refer to the minimum C / N required to achieve the Quasi Error Free (QEF) condition. The QEF criteria applied to the estimation results may match the QEF criteria used to measure SISO performance data. In this case, the SISO performance data has a BER = 10 -6 (i.e., FER = 10 -4 It may be measured under ) conditions, and the MIMO C / N estimates derived based on this can be interpreted as guaranteeing the same error performance.

[0620] Additionally, the SISO performance dataset that serves as the basis for MIMO performance estimation may be measured at different target error rates. In this case, the guaranteed error performance may need to follow the criteria applied to the reference data (SISO performance data).

[0621] The results of the estimation according to one embodiment of the present invention may be theoretical estimates based on the assumption that optimal MIMO detection (i.e., MIMO equalization) is achieved at the receiver. For the estimation, Maximum Likelihood (ML) MIMO equalization is assumed, and therefore, if other MIMO detection techniques such as the Minimum Mean-Square Error (MMSE) method are used, additional implementation loss may occur.

[0622] An estimation (estimation model) according to one embodiment of the present invention may be compatible with three types of channel conditions. In this case, the three types of channel conditions may be AWGN, Rayleigh (RL), and Rician (RC). An AWGN channel may represent a situation where the channel consists only of Line-of-Sight (LoS) paths, an RL channel may represent, conversely, a situation where the channel consists only of Non-LoS (NLoS) scattering components, and an RC channel may represent a case where both LoS and NLoS components are included. In this case, for the RC channel, the power ratio between the two components may be characterized by the Rician K-factor.

[0623] Formulaic descriptions for the channel models considered are described in Table 9 and Equations 7, 8, and 9 below.

[0624] Channel ModelFormulaic DescriptionAWGN (Full-LoS)H AWGN RLH RL RCH RC

[0625] [Mathematical Formula 7]

[0626]

[0627] [Mathematical Formula 8]

[0628]

[0629] [Mathematical Formula 9]

[0630]

[0631] At this time, ρ L It can represent a parameter that identifies the power portion of co-polarization and cross-polarization components in the LoS part of the MIMO channel. This value is XPD L It can be determined by.

[0632] At this time, ρ N It can represent a parameter that identifies the power ratio of co-polarization and cross-polarization components in the NLoS part of the MIMO channel. This value is XPD N It can be determined by.

[0633] At this time, XPD L It can represent the XPD evaluated in the LoS portion of the MIMO channel and can be described in dB units.

[0634] At this time, XPD N It can represent the XPD evaluated in the NLoS portion of the MIMO channel and can be described in dB units.

[0635] At this time, g 00 , g 10 , g 01 and g 11can represent the normalized random fading gains at each MIMO channel entity, and these can be iid (independent and identically distributed) complex Gaussian random variables with a zero-mean and unit variance.

[0636] In this case, K can be a Rician K-factor, and K can be 10.

[0637] In the following, XPD can be described in terms of channel XPD incorporating all cross-polarization effects introduced from antennas and propagation paths. Herein, XPD may represent the ratio between the same-polarization channel power and the cross-polarization channel power.

[0638] ρ L , ρ N , XPD L , and XPD N The relationship between them is XPD L = 10 log 10 (ρ L / (1 - ρ L )) and XPD N = 10 log 10 (ρ N / (1 - ρ N This can be rewritten as in the following mathematical formula 10.

[0639] [Mathematical Formula 10]

[0640]

[0641] According to one embodiment of the present invention, not only an ideal estimation assuming complete Channel State Information (CSI) but also an estimation for a CSI environment where errors exist can be provided. At this time, as previously mentioned, the estimation model can be classified into the following two classes depending on the availability of CSI.

[0642] - Class P: Complete CSIR (Channel State Information at the Receiver) is assumed

[0643] - Class E: Considers channel estimation error

[0644] In this case, while the pilot boosting effect can be used in Class E, Class P may not consider (neglect) the channel estimation operation.

[0645] Both classes can be modeled based on samples of representative channel conditions. For example, supported channel conditions can be listed in Table 10 below.

[0646] Channel ModelXPD Configuration Θ XPD XPD in LoS components: XPD L XPD in NLoS components: XPD N AWGNAny values ​​are applicable if XPD L ≥ 0 dBNot Defined (NLoS signals absent)RayleighNot Defined (LoS signals absent)20 dB10 dB5 dB0 dBRician20 dB20 dB10 dB5 dB0 dB10 dB10 dB5 dB0 dB

[0647] The estimation model can present a unified structure compatible across its subdivided classes and available channel conditions.

[0648] A general procedure is a set of input variables (τ SISO , ChMod, Θ XPD from τ MIMO It can derive.

[0649] At this time, τ MIMO can represent the linear scale expression of the C / N estimate required in a MIMO system. The dB scale expression of this C / N value is 10log 10 τ MIMO It can be given as.

[0650] At this time, τ SISO can represent a linear scale representation of the reference C / N requirement measured in SISO systems. In this case, τ SISO This may specifically refer to AWGN channel measurements, and when Annex A of the ATSC 3.0 A / 324 document is referenced, the values ​​in the 'Lab test' or 'Simulation' rows of Table A.3.2 may be used. This value corresponds to the measurement obtained without applying LDM and pilot boosting. The dB scale representation of this C / N value is 10log 10 τ SISO It can be given as.

[0651] In this case, ChMod may be a parameter that identifies the channel model condition. For example, ChMod ∈ {AWGN, RL, RC}.

[0652] At this time, Θ XPD can be a parameter identifying the channel XPD configuration and can be defined dependently on the channel model. For example, if ChMod = AWGN, then Θ XPD = XPD L ∈ {20, 10, 5, 0}, and if ChMod = RL, then Θ XPD = XPD N ∈ {20, 10, 5, 0}, and if ChMod = RC, then Θ XPD = (XPD L , XPD N )(Available value pairs are described in Table 10 above) may be.

[0653] When LDM is applied, τ for the core layer and enhanced layer MIMO The values ​​can be obtained individually. In this case, the estimation model may require the injection level (IL) as an input variable, and IL may represent the injection level described in dB scale. This value may be determined by L1D_plp_ldm_injection_level, which is included in the preamble and signaled.

[0654] For LDM examples, performance estimation according to one embodiment of the present invention may only support first-type layered MIMO.

[0655] Input variables F for the Class E estimation model PB , D X and D Y may be additionally required. In this case, F PBcan represent the dB-scale power of pilot boosting applied to scattered pilots. This value is D X and D Y It can be determined by L1D_scattered_pilot_boost (or L1B_first_sub_scattered_pilot_boost) combined with. In this case, D X may refer to the frequency domain separation of pilot-bearing carriers and can be determined by the L1D_scattered_pilot_pattern (or L1B_first_sub_scattered_pilot_pattern). In this case, D Y may be the time domain separation of pilot-bearing cells, that is, it may represent the number of symbols forming one scattered pilot sequence. D Y can be determined by L1D_scattered_pilot_pattern (or L1B_first_sub_scattered_pilot_pattern).

[0656] At this time, the reference C / N τ SISO Values ​​measured on an unfaded channel may need to be used. When Annex A of the ATSC 3.0 A / 324 document is referenced, values ​​from the 'Lab test' or 'Simulation' rows of Table A.3.2 may be used.

[0657] Since the values ​​in Annex A of the ATSC 3.0 A / 324 document are recorded in the dB scale, τ SISOBefore being used, it can be converted to a linear scale as shown in Equation 11 below.

[0658] [Mathematical Formula 11]

[0659]

[0660] Conversely, the calculated τ MIMO It can be converted to a dB scale as shown in Equation 12 below.

[0661] [Mathematical Formula 12]

[0662] dB Scale Estimate of Required C / N in MIMO System [dB] = 10log 10 τ MIMO

[0663] First, we will explain the estimation assuming complete CSI (Class P model).

[0664] Class P estimates assuming a perfect CSIR with no channel estimation error can be considered as the theoretical limit that each ModCod combination can achieve in ATSC 3.0 MIMO.

[0665] A generalized formula for estimating Class P can be presented as shown in Equation 13 below.

[0666] [Mathematical Formula 13]

[0667]

[0668] When LDM is not applied, the linear scale formulation can be written as shown in Equation 14 below.

[0669] [Mathematical Formula 14]

[0670]

[0671] The intermediate estimate ζ used in the above mathematical formula 14 can be expressed as in the following mathematical formula 15.

[0672] [Mathematical Formula 15]

[0673]

[0674] In addition, the correction offset function f used in the above mathematical formula 14 CO ChMod (ζ dB |Θ XPD ζ in ) dB = 10log 10 It can be ζ. In this case, each ChMod realization (i.e., AWGN, RL, or RC) has a unique f CO ChMod (ζ dB |Θ XPD It can have ). The correction offset function corresponding to each ChMod will be described later.

[0675] At this time, the parameters ε R and Ω ChMod are respectively τ SISO And according to ChMod, it can be written as in the following mathematical formulas 16 and 17.

[0676] [Mathematical Formula 16]

[0677]

[0678] [Mathematical Formula 17]

[0679]

[0680] At this time, Ω ChMod Each realization of Ω ChMod ) may be a scalar coefficient determined solely by XPD values. The scalar coefficients corresponding to each ChMod will be described later.

[0681] τ MIMO The estimation procedure for calculating can be expressed as shown in pseudocode 1 below.

[0682]

[0683] [Pseudocode 1]

[0684] Input: τ SISO , ChMod, Θ XPD

[0685] Initialization: Compute ε R and Ω ChMod

[0686] Step i: Compute ζ using equation 15

[0687] Step ii: Obtain τ MIMO by applying f CO ChMod (ζ dB |Θ XPD ), using ζ dB = 10log 10 ζ

[0688] Output: τ MIMO

[0689]

[0690] Since only LoS components exist in AWGN channels, the effective XPD in AWGN channels is XPD L It can be directly identical to. For AWGN channels, XPD N may not be defined. In this case, Θ XPD = XPD L It could be.

[0691] According to the above mathematical formula 10, ρ L Given this, the parameter Ω ChMod It can be expressed as shown in the following mathematical formula 18.

[0692] [Mathematical Formula 18]

[0693] Ω AWGN = (2ρ L - 1) 2

[0694] For all cases of the AWGN channel, f CO ChMod (ζ dB |Θ XPD ) = 0, and this is any ζ dB and Θ XPDIt also holds true for.

[0695] Therefore, the following mathematical formula 19 can simply hold in the AWGN channel.

[0696] [Mathematical Formula 19]

[0697] τ MIMO =

[0698]

[0699] In this case, under AWGN channel conditions, this estimation model is 1 / 2 < ρ L All real values ​​ρ within the range ≤1 L This allows all XPD when an AWGN environment is considered. L ≥ 0 may mean that it is supported.

[0700] Unlike AWGN channels, only NLoS components can exist in RL channels. In RL channels, the effective XPD is XPD N It can be directly identical to. For RL channels, XPD L may not be defined. In this case, Θ XPD = XPD N It could be.

[0701] According to the above mathematical formula 10, ρ N Given this, the parameter Ω ChMod It can be expressed as shown in the following mathematical formula 20.

[0702] [Mathematical Formula 20]

[0703] Ω RL = ρ N 2 + (1 - ρ N ) 2

[0704] Under RL channel conditions, the correction offset function of the following Equation 21 can be applied to the above Equation 14 (see Step ii of the above pseudocode 1).

[0705] [Mathematical Formula 21]

[0706]

[0707] At this time, f CO RL (ζ dB |Θ XPD Refer to Table 11 below for the coefficients c5, c4, ..., c0 constituting ). In this case, these coefficient values ​​are XPD N Dependent on (specific to XPD N ) may be. Table 11 below shows f with respect to XPD levels. CO RL (ζ dB |Θ XPD Represents the coefficients of ).

[0708] XPD Configuration: XPD N Coefficientsc5c4c3c2c1c020 dB-1.237 * 10 -7 1.156 * 10 -5 -3.366 * 10 -4 8.187 * 10 -4 0.1170.981310 dB-1.263 * 10 -7 1.225 * 10 -5 -3.841 * 10 -4 2 * 10 -3 0.1080.85185 dB -9.448 * 10 -8 1.005 * 10 -5 -3.544 * 10 -4 2.814 * 10 -3 8.911 * 10 -2 0.65480 dB - 5.598 * 10 -8 7.061 * 10 -6 -2.891 * 10 -4 2.997 * 10 -3 6.902 * 10 -2 0.4957

[0709] The above mathematical formula 21 is ζ dB f when ≥ 30dB CO RL (ζ dB |ΘXPD ) is f sat RL Saturated by f sat RL It represents ). Table 12 below shows XPD N f according to sat RL It represents.

[0710] XPD Configuration: XPD N f sat RL [dB]20 dB2.510 dB2.425 dB2.140 dB1.83

[0711] The RC(Rician) channel can represent a compound of the AWGN channel response and the RL channel response, in which both LoS and NLoS components are present.

[0712] In RC channels, XPD L and XPD N Since this is realized individually, the XPD condition Θ XPD = (XPD L , XPD N ) is XPD L and XPD N It can be defined as a pair composed of. In this case, the effective XPD can be derived in the manner described below. According to the above mathematical formula 10, ρ L and ρ N Given this, the parameter Ω ChMod It can be expressed as shown in the following mathematical formula 22.

[0713] [Mathematical Formula 22]

[0714]

[0715] In this case, the Rician K-factor K can be set to 10.

[0716] Under RC channel conditions, the correction offset function of the following Equation 23 can be applied to the above Equation 14 (see Step ii of the above pseudocode 1).

[0717] [Mathematical Formula 23]

[0718]

[0719] At this time, f CO RC (ζ dB |Θ XPD Refer to Table 12 below for the coefficients c5, c4, ..., c0 constituting ). In this case, these coefficient values ​​are (XPD L , XPD N ) specific to the pair (XPD L , XPD N )) may be. Table 13 below shows f with respect to XPD levels. CO RC (ζ dB |Θ XPD Represents the coefficients of ).

[0720] XPD ConfigurationCoefficientsXPD L XPD N c5c4c3c2c1c020 dB20 dB-2.504 * 10 -8 2.234 * 10 -6 -5.701 * 10 -5 -1.261 * 10 -4 2.266 * 10 -2 0.191610 dB - 1.961 * 10 -8 1.782 * 10 -6 -4.566 * 10 -5 -1.64 * 10 -4 2.088 * 10 -2 0.17665 dB - 1.784 * 10 -8 1.625 * 10 -6 -4.239 * 10 -5 -9.539 * 10 -5 1.764 * 10 -2 0.14780 dB - 1.073 * 10 -8 9.887 * 10 -7 -2.627 * 10 -5-6.453 * 10 -5 1.193 * 10 -2 9.908 * 10 -2 10 dB 10 dB - 3.442 * 10 -8 3.416 * 10 -6 -1.072 * 10 -4 5.958 * 10 -4 2.508 * 10 -2 0.17515 dB -2.896 * 10 -8 2.944 * 10 -6 -9.511 * 10 -5 5.922 * 10 -4 2.127 * 10 -2 0.14660 dB - 1.965 * 10 -8 2.109 * 10 -6 -7.294 * 10 -5 5.714 * 10 -4 1.458 * 10 -2 9.731 * 10 -2

[0721] Also, ζ dB f when ≥ 30dB CO RC (ζ dB |Θ XPD ) is f sat RC Saturated by f sat RC ) represents. Table 14 below shows (XPD L , XPD N f according to ) sat RC It represents.

[0722] XPD Configuration sat RC [dB]XPD L XPD N 20 dB20 dB0.4210 dB0.395 dB0.330 dB0.2310 dB10 dB0.55 dB0.430 dB0.31

[0723] The following describes the estimation of Class P for a MIMO system with LDM applied. All LDM examples described below can be assumed to be layered MIMO, which is the combined use of LDM and MIMO. In this case, the estimation model can be specifically applied to Type 1 layered MIMO, which uses MIMO in both the core layer and the enhanced layer. Here, for each LDM layer, τ MIMO Each can be identified.

[0724] τ of the core layer of layered multiplexed signals MIMO 는 τ MIMO | LDM CL It can be designated as. This can be expressed as in Equation 24 below.

[0725] [Mathematical Formula 24]

[0726]

[0727] In this case, the latent variable ζ ^ CL is another latent variable ζ CL and f CO ChMod (ζ CL dB |Θ XPD Based on ), it can be expressed as in the following mathematical formula 25.

[0728] [Mathematical Formula 25]

[0729]

[0730] At this time, f identical to the above pseudocode 1 CO ChMod (·) can be used, and the input ζ CL dB = 10log 10 ζ CL It can be. In this case, ζ CL It can be expressed as shown in mathematical formula 26 below.

[0731] [Mathematical Formula 26]

[0732]

[0733] At this time, ζ CL Parameters determining ζ and Δ LDM Each can be expressed as shown in the following mathematical formulas 27 and 28.

[0734] [Mathematical Formula 27]

[0735]

[0736] [Mathematical Formula 28]

[0737]

[0738] At this time, ε R and Ω ChMod This has already been explained in the above mathematical formulas 16 and 17.

[0739] In this case, IL can be the injection level of LDM.

[0740] τ of the core layer MIMO The estimation procedure for calculating can be expressed as shown in pseudocode 2 below.

[0741]

[0742] [Pseudocode 2]

[0743] Input: τ SISO , ChMod, Θ XPD , IL

[0744] Initialization: Compute ε R , Ω ChMod , and Δ LDM using equations 16, 17, and 28

[0745] Step i: Compute ζ using equation 27

[0746] Step ii: Convert ζ into ζ CL using equation 26

[0747] Step iii: Obtain ζ^ CL by applying f CO ChMod (ζ CL dB |Θ XPD ), using ζ CL dB = 10log 10 ζ CL and equation 25

[0748] Step iv: Obtain τ MIMO | LDM CL from equation 24

[0749] Output: τ MIMO | LDM CL

[0750]

[0751] In this case, when ChMod = AWGW, τ MIMO | LDM CL is directly agree with ζ (i.e., τ MIMO | LDM CL = ζ)can.

[0752] At this time, τ SISO The value may correspond to the measurement obtained without applying LDM.

[0753] τ for the enhanced layer of LDM MIMO ul τ MIMO | LDM EL When denoted as such, it can be expressed as shown in the following mathematical formula 29.

[0754] [Mathematical Formula 29]

[0755]

[0756] In this case, the parameters ζ, Δ LDM and ε R can be obtained by the above mathematical formulas 15, 28, and 16, respectively. At this time, Ω identical to the above pseudocode 1ChMod and f CO ChMod (·) can be used.

[0757] Estimation for the enhanced layer proceeds in the same manner as described in Pseudocode 1, but the result is additionally Δ LDM Divided by. The τ of the enhanced layer MIMO The estimation procedure for calculating can be expressed as shown in pseudocode 3 below.

[0758]

[0759] [Pseudocode 3]

[0760] Input: τ SISO , ChMod, Θ XPD , IL

[0761] Initialization: Compute ε R , Ω ChMod , and Δ LDM using equations 16, 17, and 28

[0762] Step i: Compute ζ using equation 15

[0763] Step ii: Obtain τ MIMO | LDM EL by applying f CO ChMod (ζ dB |Θ XPD ) to ζ / Δ LDM using equations 29

[0764] Output: τ MIMO | LDM EL

[0765]

[0766] At this time, τ SISO The value may correspond to the measurement obtained without applying LDM.

[0767] Calculation examples are explained in detail below.

[0768] The calculation examples are based on the following premises.

[0769] τ SISO 1.9588 (=2.92 dB)

[0770] ChMod RL

[0771] Θ XPD XPD N = 10 dB (XPD L = N / A)

[0772] At this time, the τ being considered SISO The value may correspond to the ModCod combinations described in Table 15 below. In this case, the simulation results presented in Table A.3.2 of the ATSC 3.0 A / 324 document may be used. In this case, the target QEF condition is BER = 10 -6 It can be inherited as is.

[0773] Constellation16QAMInner CodeLDPC Code (Code Length: 64,800 bits, Code Rate: 5 / 15)Outer CodeBCH Code

[0774] Based on the above input parameters, the initialization step can calculate the parameters as follows.

[0775] ε R = 1 + 2 * 1.9588 + (1.9588) 2 = 8.7548

[0776] ρ N = 10 (10 / 10) / (1 + 10 (10 / 10) ) = 0.9091

[0777] Ω RL = (0.9091) 2 + (1 - 0.9091) 2 = 0.8347

[0778] These parameter values ​​can be applied equally to both non-LDM and LDM examples.

[0779] Based on the above set of parameters, Class P estimation for a non-LDM configuration can be performed as follows.

[0780] First, ζ can be calculated as shown in the following mathematical formula 30.

[0781] [Mathematical Formula 30]

[0782]

[0783] Therefore, ζ dB = 10log 10 2.0770 = 3.1743.

[0784] Also, f CO RL (ζ dB |Θ XPD ) is f CO RL (3.1743|XPD N = 10dB) = -1.263 * 10 -7 * (3.1743) 5 + 1.225 * 10 -5 * (3.1743) 4 - 3.841 * 10 -4 * (3.1743) 3 + 2 * 10 -3 * (3.1743) 2 It can be calculated as + 0.108 * (3.1743) + 0.8518 = 1.2037.

[0785] Ultimately, the estimated value τ MIMO 는 τ MIMO It is calculated as = 2.0770 * 10(1.2037 / 10)= 2.7403, which is the dB scale estimate 10log 10 τ MIMO = 4.3780 dB.

[0786] For the LDM example, the injection level IL can be assumed to be 10 dB.

[0787] At this time, the initialization step additionally includes the parameter Δ LDM = 10 -(10 / 10) / (1 + 10 -(10 / 10) ) = 0.0909 can be prepared.

[0788] This LDM parameter value can be commonly applied to core layer and enhanced layer examples.

[0789] ζ for the core layer can be calculated as in Equation 31 below, and 2.9120 can be obtained.

[0790] [Mathematical Formula 31]

[0791]

[0792] At this time, ζ CL and ζ CL dB is ζ CL = ((1-0.0909)*2.9120) / (1+0.0909*2.9120) = 2.0932 and ζ CL dB = 10log 10 It can be obtained as 2.0932 = 3.2080.

[0793] At this time, f CO RL (ζ CL dB |Θ XPD ) is f CO RL (3.2080|XPD N = 10dB) = -1.263 * 10 -7 * (3.2080) 5 + 1.225 * 10 -5 * (3.2080) 4 - 3.841 * 10 -4 * (3.2080) 3 + 2 * 10 -3 * (3.2080) 2 It can be calculated as + 0.108 * (3.2080) + 0.8518 = 1.2074.

[0794] At this time, ζ ^CL is ζ ^ CL It can be calculated as = 2.0932 * 10(1.2074 / 10)= 2.7641.

[0795] Ultimately, the estimated value τ MIMO | LDM CL τ MIMO | LDM CL It is calculated as = 2.7641 / (1-0.0909-0.0909*2.7641) = 4.2019, which is the dB scale estimate 10log 10 τ MIMO | LDM CL = 6.2344 dB.

[0796] ζ and ζ for enhanced layer dB is calculated as explained through the above mathematical formula 30, so ζ = 2.0770 and ζ dB = 3.1743 can be obtained.

[0797] At this time, f CO RL (ζ dB |Θ XPD ) is f CO RL (3.1743|XPD N = 10dB) = -1.263 * 10 -7 * (3.1743) 5 + 1.225 * 10 -5 * (3.1743) 4 - 3.841 * 10 -4 * (3.1743) 3 + 2 * 10 -3 * (3.1743) 2 It can be calculated as + 0.108 * (3.1743) + 0.8518 = 1.2037.

[0798] Ultimately, the estimated value τ MIMO | LDM EL τ MIMO | LDM EL It is calculated as = (2.0770 / 0.0909) * 10(1.2037 / 10)= 30.147, which is the dB scale estimate 10log10 τ MIMO | LDM EL = 14.792 dB.

[0799] Below, we describe an estimation (Class E model) that considers erroneous CSIR.

[0800] The magnitude of CSI errors is modeled through the actual channel estimation process, which allows for comprehensive scaling based on the impact of pilot boosting on system performance. In this case, the Class E method can assume theoretical channel estimation behavior, namely linear MMSE estimation. System performance in commercial receivers may vary to some extent depending on the implemented channel estimation method.

[0801] In the following, the referenced τ SISO The value may correspond to measurements obtained without applying LDM and pilot boosting.

[0802] Under AWGN channel conditions, channel estimation error can be ignored. In this case, the Class E estimation can be the same as the Class P estimation for the AWGN channel unless pilot boosting is applied.

[0803] When the pilot boosting effect is applied, the estimation result is τ MIMO = ζ / κ d It can be. In this case, ζ can be expressed as in Equation 15 above, and κ d It can be expressed as shown in the following mathematical formula 32.

[0804] [Mathematical Formula 32]

[0805]

[0806] At this time, κ dThis may be a quantification of the power reduction at the data cells that offsets boosted pilots.

[0807] At this time, A SP represents the amplitude in scattered pilot cells, and the pilot boosting power F as shown in Equation 33 below. PB It can be expressed based on (reliant on).

[0808] [Mathematical Formula 33]

[0809]

[0810] At this time, F PB is a distributed pilot pattern (D x and D y It can be determined by L1D_scattered_pilot_boost (or L1B_first_sub_scattered_pilot_boost) combined with ).

[0811] In this case, since the unboosted pilot power can be normalized to 1, A in the context of pilot boosting SP This can be interpreted as amplitude gain.

[0812] As mentioned above, only the NLoS component can exist in the RL channel. In this case, Θ XPD = XPD N It can be, and the above mathematical formula 20 may hold. In this case, ρ N It can be given by the above mathematical formula 10.

[0813] τ under RL channel conditions (i.e., ChMod = RL) MIMO It can be expressed as shown in the following mathematical formula 34.

[0814] [Mathematical Formula 34]

[0815]

[0816] At this time, A SP and κ d Each can refer to the above mathematical formulas 33 and 32.

[0817] At this time, ζ ^ It can be expressed as shown in the following mathematical formula 35.

[0818] [Mathematical Formula 35]

[0819]

[0820] If pilot boosting is not applied, the above Equation 34 can be simplified as shown in Equation 36 below.

[0821] [Mathematical Formula 36]

[0822]

[0823] In this case, the intermediate estimate ζ ^ It can be described as Equation 35 using another intermediate estimate ζ of Equation 37 below and the correction offset function of Equation 38 below.

[0824] [Mathematical Formula 37]

[0825]

[0826] [Mathematical Formula 38]

[0827]

[0828] At this time, ε R is as in the above mathematical formula 16, τ SISO It can be determined from, and ζ dB = 10log 10 It could be ζ.

[0829] At this time, this f CO RL|CE (·) is the aforementioned f CO RL It may differ from (·). In this case, f CORL|CE (ζ dB |Θ XPD Refer to Table 16 below for the coefficients c5, c4, ..., c0 constituting ). That is, Table 16 shows f according to XPD levels. CO RL|CE (ζ dB |Θ XPD Represents the coefficients of ).

[0830] XPD Configuration: XPD N Coefficientsc5c4c3c2c1c020 dB-1.761 * 10 -7 1.571 * 10 -5 -4.391 * 10 -4 1.377 * 10 -3 0.12550.905610 dB-1.6 * 10 -7 1.485 * 10 -5 -4.469 * 10 -4 2.345 * 10 -3 0.11490.78235 dB -1.072 * 10 -7 1.141 * 10 -5 -4.008 * 10 -4 3.255 * 10 -3 9.319 * 10 -2 0.58740 dB - 6.628 * 10 -8 8.22 * 10 -6 -3.313 * 10 -4 3.483 * 10 -3 7.17 * 10 -2 0.4319

[0831] In the above mathematical formula 38, ζ dB f when ≥ 30dB CO RL|CE (ζ dB |Θ XPD ) is f sat RL|CE Saturated by f sat RL|CE ) can be. Table 17 below shows XPD N f according to sat RL|CEIt represents.

[0832] XPD Configuration: XPD N f sat RL|CE [dB]20 dB2.510 dB2.415 dB2.140 dB1.83

[0833] In summary, compared to the Class P process, the Class E method may include one additional step of deriving Equation 34 from Equation 35. The estimation procedure can be summarized as shown in the following pseudocode 4.

[0834]

[0835] [Pseudocode 4]

[0836] Input: τ SISO , ChMod = RL, Θ XPD , F PB , D x , D y

[0837] Initialization: Compute ε R , Ω RL , A SP , κ d using equations 16, 20, 33 and 32

[0838] Step i: Compute ζ using equation 37

[0839] Step ii: Obtain ζ ^ by applying f CO RL|CE (ζ dB |Θ XPD ), using ζ dB = 10log 10 ζ and equation 35

[0840] Step iii: Convert ζ ^ into τ MIMO using equation 34

[0841] Output: τMIMO

[0842]

[0843] Both LoS and NLoS components can exist in the RC channel. In this case, XPD L and XPD N can be individually defined, and pairs of these are Θ XPD = (XPD L , XPD N ) can be configured. In the RC embodiment, Ω RC can be given by the above mathematical formula 22. In this case, ρ L and ρ N Refer to the above mathematical formula 10.

[0844] τ under RC channel conditions (i.e., ChMod = RC) MIMO It can be expressed as shown in the following mathematical formula 39.

[0845] [Mathematical Formula 39]

[0846]

[0847] At this time, A SP and κ d Each can refer to the above mathematical formulas 33 and 32.

[0848] At this time, ζ ^ It can be expressed as shown in the following mathematical formula 40.

[0849] [Mathematical Formula 40]

[0850]

[0851] In this case, the intermediate estimate ζ ^ It can be described as Equation 40 above using another intermediate estimate ζ of Equation 41 below and the correction offset function of Equation 42 below.

[0852] [Mathematical Formula 41]

[0853]

[0854] [Mathematical Formula 42]

[0855]

[0856] At this time, ε R is as in the above mathematical formula 16, τ SISO It can be determined from, and ζ dB = 10log 10 It could be ζ.

[0857] At this time, this f CO RC|CE (·) is the aforementioned f CO RC It may differ from (·). In this case, f CO RC|CE (ζ dB |Θ XPD Refer to Table 18 below for the coefficients c5, c4, ..., c0 constituting ). In this case, the coefficient values ​​are (XPD L , XPD N It can be specific to ). That is, Table 18 shows f according to XPD levels. CO RC|CE (ζ dB |Θ XPD Represents the coefficients of ).

[0858] XPD ConfigurationCoefficientsXPD L XPD N c5c4c3c2c1c020 dB20 dB000-5.331 * 10 -6 3.715 * 10 -4 0.41610 dB00-1.296 * 10 -6 8.327 * 10 -5 -1.628 * 10 -3 0.39825 dB00 -3.408 * 10 -6 2.372 * 10 -4 -5.249 * 10 -3 0.36580 dB 3.05 * 10 -8 -2.178 * 10 -6 4.31 * 10-5 1.382 * 10 -4 -1.185 * 10 -2 0.314910 dB10 dB07.126 * 10 -8 -2.277 * 10 -6 -1.175 * 10 -4 5.261 * 10 -3 0.45445 dB000-1.566 * 10 -5 1.07 * 10 -3 0.42140 dB2.311 * 10 -8 -1.652 * 10 -6 3.44 * 10 -5 5.056 * 10 -6 -6.783 * 10 -3 0.367

[0859] In the above mathematical formula 42, ζ dB ≥ Th(Θ XPD f when ) CO RC|CE (ζ dB |Θ XPD ) is f sat RC|CE Saturated by f sat RC|CE ) can be. Table 19 below shows Θ XPD f according to sat RC|CE and Th(Θ XPD Represents the values.

[0860] XPD Configuration sat RC|CE [dB]Th(Θ XPD ) [dB]XPD L XPD N 20 dB20 dB0.422510 dB0.39205 dB0.33200 dB0.222010 dB10 dB0.5205 dB0.44300 dB0.3120

[0861] The estimation procedure can be summarized as shown in pseudocode 5 below.

[0862]

[0863] [Pseudocode 5]

[0864] Input: τ SISO , ChMod = RC, K = 10, Θ XPD , F PB , D x , D y

[0865] Initialization: Compute ε R , Ω RC , A SP , κ d using equations 16, 22, 33 and 32

[0866] Step i: Compute ζ using equation 41

[0867] Step ii: Obtain ζ ^ by applying f CO RC|CE (ζ dB |Θ XPD ), using ζ dB = 10log 10 ζ and equation 40

[0868] Step iii: Convert ζ ^ into τ MIMO using equation 39

[0869] Output: τ MIMO

[0870]

[0871] Hereinafter, Class E estimation for a Type 1 layered MIMO system is described. At this time, τ for the core layer and the enhanced layer MIMO They can be identified.

[0872] Below, the parameters ε R , Δ LDM , A SP , κ d It follows the previously defined content, and may refer to mathematical formulas 16, 28, 33, and 32, respectively.

[0873] At this time, τ SISO This may correspond to measurements obtained without applying LDM and pilot boosting.

[0874] Similar to Class P estimation for Type 1 layered MIMO, the τ of the core layer in Class E estimation as well. MIMO 는 τ MIMO | LDM CL It can be expressed as follows.

[0875] When ChMod = AWGN, the estimated C / N value can be expressed as shown in Equation 43 below.

[0876] [Mathematical Formula 43]

[0877]

[0878] At this time, Ω AWGN , = (2ρ L - 1) 2 It could be.

[0879] τ MIMO | LDM CL The estimation process for calculating can be summarized as shown in pseudocode 6 below.

[0880]

[0881] [Pseudocode 6]

[0882] Input: τ SISO , ChMod = AWGN, Θ XPD , F PB , D x , D y , IL

[0883] Initialization: Compute ε R , Ω AWGN , A SP , κ d , and Δ LDM

[0884] Step i: Compute equation 43 to obtain τ MIMO | LDM CL : Calculate ζ and divide it by κd

[0885] Output: τ MIMO | LDM CL

[0886]

[0887] τ under RL channel conditions MIMO | LDM CL It can be expressed as shown in the following mathematical formula 44.

[0888] [Mathematical Formula 44]

[0889]

[0890] At this time, ζ r It can be expressed as shown in the following mathematical formula 45.

[0891] [Mathematical Formula 45]

[0892]

[0893] At this time, ζ ^ CL It can be expressed as shown in the following mathematical formula 46.

[0894] [Mathematical Formula 46]

[0895]

[0896] At this time, ζ CL is as explained in the above mathematical formula 26, and f CO RL|CE (ζ CL dB |Θ XPD ) is f explained in the above mathematical formula 38. CO RL|CE ζ as input to (·) CL dB = 10log 10 ζ CL It can correspond to the result of applying it.

[0897] At this time, the intermediate estimate ζ can be expressed as shown in Equation 47 below.

[0898] [Mathematical Formula 47]

[0899]

[0900] At this time, the above mathematical formulas 10 and 20 can be shared.

[0901] τ of Type 1 layered MIMO under RL channel conditions MIMO | LDM CL The Class E estimation process for calculating can be summarized as shown in pseudocode 7 below.

[0902]

[0903] [Pseudocode 7]

[0904] Input: τ SISO , ChMod = RL, Θ XPD , F PB , D x , D y , IL

[0905] Initialization: Compute ε R , Ω RL , A SP , κ d , and Δ LDM

[0906] Step i: Compute ζ using equation 47

[0907] Step ii: Convert ζ into ζ CL using equation 26

[0908] Step iii: Obtain ζ ^ CL by applying f CO RL|CE (ζ CL dB |Θ XPD ), using ζ CL dB = 10log 10 ζ CL and equation 46

[0909] Step iv: Convert ζ ^ CL into ζ r using equation 45

[0910] Step v: Obtain τ MIMO | LDM CL from equation 44

[0911] Output: τ MIMO | LDM CL

[0912]

[0913] τ under RC channel conditions MIMO | LDM CL It can be expressed as shown in the following mathematical formula 48.

[0914] [Mathematical Formula 48]

[0915]

[0916] At this time, ζ r It can be expressed as in the above mathematical formula 45.

[0917] At this time, ζ ^ CL It can be expressed as shown in the following mathematical formula 49.

[0918] [Mathematical Formula 49]

[0919]

[0920] At this time, ζ CL is as explained in the above mathematical formula 26, and f CO RC|CE (ζ CL dB |Θ XPD ) is f explained in the above mathematical formula 42. CO RC|CE ζ as input to (·) CL dB = 10log 10 ζ CL It can correspond to the result of applying it.

[0921] At this time, the intermediate estimate ζ can be expressed as shown in Equation 50 below.

[0922] [Mathematical Formula 50]

[0923]

[0924] At this time, the above mathematical formulas 10 and 22 may be shared.

[0925] τ of Type 1 layered MIMO under RC channel conditions MIMO | LDM CL The Class E estimation process for calculating can be summarized as shown in pseudocode 8 below.

[0926]

[0927] [Pseudocode 8]

[0928] Input: τ SISO , ChMod = RC, Θ XPD , F PB , D x , D y , IL

[0929] Initialization: Compute ε R , Ω RC , A SP , κ d , and Δ LDM

[0930] Step i: Compute ζ using equation 50

[0931] Step ii: Convert ζ into ζ CL using equation 26

[0932] Step iii: Obtain ζ ^ CL by applying f CO RC|CE (ζ CL dB |Θ XPD ), using ζ CL dB = 10log 10 ζ CL and equation 49

[0933] Step iv: Convert ζ ^ CL into ζ r using equation 45

[0934] Step v: Obtain τ MIMO | LDM CL from equation 48

[0935] Output: τ MIMO | LDM CL

[0936]

[0937] τ MIMO | LDM EL τ of this enhanced layer MIMO When representing this, it can be described according to channel conditions as shown in the following mathematical formulas 51, 52, 53, and 54.

[0938] [Mathematical Formula 51]

[0939]

[0940] [Mathematical Formula 52]

[0941]

[0942] [Mathematical Formula 53]

[0943]

[0944] [Mathematical Formula 54]

[0945]

[0946] In this case, the intermediate estimate ζ EL It can be expressed as shown in the following mathematical formula 55.

[0947] [Mathematical Formula 55]

[0948]

[0949] At this time, ζ can be expressed as in the above mathematical formula 15.

[0950] At this time, f CO ChMod|CE (ζ dB |Θ XPD f of ) CO ChMod|CE(·) may be as described above regarding the Class E estimation in the case where LDM is not applied for each ChMod realization.

[0951] At this time, Ω ChMod Refer to the above mathematical formulas 18, 20, and 22.

[0952] In this case, the overall estimation for the LDM enhanced layer is similar to the Class E estimation of the aforementioned non-LDM case, but during the estimation process, 1 / Δ LDM There may be a difference in that the scaling of ζ by is included.

[0953] The entire process of Class E estimation for the enhanced layer can be summarized as shown in pseudocode 9 below.

[0954]

[0955] [Pseudocode 9]

[0956] Input: τ SISO , ChMod, Θ XPD , F PB , D x , D y , IL

[0957] Initialization: Compute ε R , Ω ChMod , A SP , κ d , and Δ LDM

[0958] Step i: Compute ζ according to ChMod using equation 15

[0959] Step ii: Convert ζ into ζ EL using f CO ChMod|CE (ζ CL dB |Θ XPD ) and Δ LDM

[0960] Step iii: Obtain τMIMO | LDM EL from ζ EL using equation 51

[0961] Output: τ MIMO | LDM EL

[0962] Below, calculation examples for Class E estimation are explained in detail.

[0963] The calculation examples are based on the following premises.

[0964] τ SISO 1.9588 (=2.92 dB)

[0965] ChMod RL

[0966] Θ XPD XPD N = 10 dB (XPD L = N / A)

[0967] F PB 5.3dB

[0968] D x 8

[0969] D y 2

[0970] At this time, the parameter setting can be based on the ModCod combination, MP8_2 pilot pattern, and L1D_scattered_pilot_boost = 100 described in Table 15 above.

[0971] Based on the above input parameters, the initialization step can calculate the parameters as follows.

[0972] ε R = 1 + 2 * 1.9588 + (1.9588) 2 = 8.7548

[0973] ρ N = 10 (10 / 10) / (1 + 10 (10 / 10) ) = 0.9091

[0974] Ω RL = (0.9091) 2 + (1 - 0.9091) 2 = 0.8347

[0975] A SP = 10 (5.3 / 20) = 1.8408

[0976] κ d = 1 / (1 - 1 / (8*2) + 1.8408 2 / (8*2)) = 0.8701

[0977] These parameter values ​​can be applied equally to both non-LDM and LDM examples.

[0978] Based on the above set of parameters, Class E estimation for a non-LDM configuration can be performed as follows.

[0979] First, ζ can be calculated as in the above mathematical formula 30.

[0980] Therefore, ζ dB = 10log 10 2.0770 = 3.1743.

[0981] Also, f CO RL|CE (ζ dB |Θ XPD ) is f CO RL|CE (3.1743|XPD N = 10dB) = -1.6 * 10 -7 * (3.1743) 5 + 1.485 * 10 -5 * (3.1743) 4 - 4.469 * 10 -4 * (3.1743) 3 + 2.345 * 10 -3 * (3.1743) 2 It can be calculated as + 0.1149 * (3.1743) + 0.7823 = 1.1578.

[0982] Also, ζ ^ ζ^ It can be calculated as = 2.0770 * 10(1.1578 / 10)= 2.7115.

[0983] Ultimately, the estimated value τ MIMO is calculated as shown in Equation 56 below, yielding 4.2828, which is the dB scale estimate 10log 10 τ MIMO = 6.3173 dB.

[0984] [Mathematical Formula 56]

[0985]

[0986] For the LDM example, the injection level IL can be assumed to be 10 dB.

[0987] At this time, the initialization step additionally includes the parameter Δ LDM = 10 -(10 / 10) / (1 + 10 -(10 / 10) ) = 0.0909 can be prepared.

[0988] This LDM parameter value can be commonly applied to core layer and enhanced layer examples.

[0989] ζ for the core layer can be calculated as in Equation 31 above, and 2.9120 can be obtained.

[0990] At this time, ζ CL and ζ CL dB is ζ CL = ((1-0.0909)*2.9120) / (1+0.0909*2.9120) = 2.0932 and ζ CL dB = 10log 10 It can be obtained as 2.0932 = 3.2080.

[0991] At this time, f CO RL|CE (ζ CL dB |Θ XPD ) is f CO RL|CE (3.2080|XPD N= 10dB) = -1.6 * 10 -7 * (3.2080) 5 + 1.485 * 10 -5 * (3.2080) 4 - 4.469 * 10 -4 * (3.2080) 3 + 2.345 * 10 -3 * (3.2080) 2 It can be calculated as + 0.1149 * (3.2080) + 0.7823 = 1.1618.

[0992] At this time, ζ ^ CL is ζ ^ CL It can be calculated as = 2.0932 * 10(1.1618 / 10)= 2.7352.

[0993] At this time, ζ r is ζ r It can be calculated as = 2.7352 / (1 - 0.0909 - 0.0909*2.7352) = 4.1414.

[0994] Ultimately, the estimated value τ MIMO | LDM CL It is calculated as shown in Equation 57 below, yielding 6.4159, which is the dB scale estimate 10log 10 τ MIMO | LDM CL = 8.0726 dB.

[0995] [Mathematical Formula 57]

[0996]

[0997] ζ and ζ for enhanced layer dB is calculated as explained through the above mathematical formula 30, so ζ = 2.0770 and ζ dB = 3.1743 can be obtained.

[0998] At this time, f CO RL|CE (ζ dB |Θ XPD ) is f CORL|CE (3.1743|XPD N = 10dB) = -1.6 * 10 -7 * (3.1743) 5 + 1.485 * 10 -5 * (3.1743) 4 - 4.469 * 10 -4 * (3.1743) 3 + 2.345 * 10 -3 * (3.1743) 2 It can be calculated as + 0.1149 * (3.1743) + 0.7823 = 1.1578.

[0999] At this time, ζ EL is ζ EL = (2.0770 / 0.0909) * 10 1.1578 / 10 It can be calculated as = 29.827.

[1000] Ultimately, the estimated value τ MIMO | LDM EL It is calculated as shown in Equation 58 below, yielding 43.657, which is the dB scale estimate 10log 10 τ MIMO | LDM EL = becomes 16.499 dB.

[1001] [Mathematical Formula 58]

[1002]

[1003] Below, the method for estimating channel XPD is explained in detail.

[1004] FIG. 26 is a block diagram showing an example of a device for estimating channel XPD from antenna XPD according to an embodiment of the present invention.

[1005] Referring to FIG. 26, the device for estimating channel XPD includes a channel XPD calculation unit (2610) and a channel condition calculation unit (2620).

[1006] The channel XPD calculation unit (2610) receives the transmission antenna XPD information (TRANSMIT ANTENNA XPD SPEC.), the reception antenna XPD information (RECEIVE ANTENNA XPD SPEC.), and the polarization variation rate at reflection on the propagation path (POLARIZATION VARIATION RATIO) as inputs, and calculates the LoS component channel XPD and the NLoS component channel XPD.

[1007] For example, the transmitting antenna XPD information (TRANSMIT ANTENNA XPD SPEC.) is the XPD to be described later Tx Ant It may be, and the receiving antenna XPD information (RECEIVE ANTENNA XPD SPEC.) is the XPD to be described later Rx Ant It may be. For example, the polarization fluctuation rate during reflection along the propagation path may be r, which will be described later. For example, the LoS component channel XPD is χ, which will be described later. LoS or XPD L It may be. For example, the NLoS component channel XPD is the χ to be discussed later. NLoS or XPD N It could be.

[1008] The channel condition operation unit (2620) can output LoS component channel XPD, NLoS component channel XPD, and EFFECTIVE channel XPD using channel model information (ChMod) and K.

[1009] According to an embodiment, the channel condition calculation unit (2620) generates a result of modeling a broadcast channel and provides it to the channel XPD calculation unit (2610), and the channel XPD calculation unit (2610) may calculate and output the LoS component channel XPD, NLoS component channel XPD, and Effective channel XPD based on the modeling result.

[1010] The device illustrated in FIG. 26 may be implemented using the computer system illustrated in FIG. 24. In this case, the memory of the computer system illustrated in FIG. 24 may store instructions for executing the channel XPD estimation process described below, and the processor illustrated in FIG. 24 may execute these instructions.

[1011] One or more of the LoS component channel XPD, NLoS component channel XPD, and Effective channel XPD, which are the outputs of the device of FIG. 26, can be input to the device shown in FIG. 25.

[1012] Below, a fundamental model describing MIMO channel environments is described. The described model is a stochastic model that enables abstraction of MIMO channel environments, which can enable theoretical estimations, analyses, and applications such as the aforementioned Class P and Class E estimations.

[1013] Channel distortion in this model is applied to baseband cells, and small-scale fading effects and interactions between polarization paths can be considered. Additionally, a technique is described that supports the estimation of channel XPD from the respective properties of the transmitting and receiving antenna units through the model to be discussed later.

[1014] At this time, the following description may provide a mathematical rationale for the MIMO channel model described using Table 9. By reformulating the model to be described later, the above Table 9 (including Equations 7, 8, and 9) can be obtained while maintaining equivalence.

[1015] ATSC 3.0 MIMO can be composed of two polarized paths that are spatially multiplexed relative to each other. The generic expression for this configuration is given by Equation 59 below.

[1016] [Mathematical Formula 59]

[1017]

[1018] At this time, y0 and y1 may represent received signals in terms of baseband cells associated with respective polarization chains.

[1019] In this case, x0 and x1 can represent transmit signals in terms of baseband cells associated with their respective polarization chains.

[1020] In this case, n0 and n1 may represent additional noise observed at the baseband cell level and may affect each polarization chain.

[1021] In this case, subscripts 0 and 1 may indicate associations with polarization #1 and polarization #2, respectively. This follows theoretical conventions for using techniques at the baseband cell level. Unless otherwise noted, transmitting cells x0 and x1 may be assumed to be iid unbiased complex Gaussian random variables.

[1022] At this time, the channel matrix H can be expressed as shown in Equation 60 below.

[1023] [Mathematical Formula 60]

[1024]

[1025] In this case, the diagonal elements represent co-polarization fading, and the off-diagonal elements represent the corresponding cross-polarization counterparts. These off-diagonal elements can quantify the extent to which signals with polarization converted from their original orientation contribute.

[1026] Channel XPD in this context can characterize the degree of isolation between a homopolarized signal and a cross-polarized signal. This can be described in terms of relative ratios when expressed in a dB scale, as shown in Equation 61 below.

[1027] [Mathematical Formula 61]

[1028]

[1029] In this case, the operator E[·] can represent the expectation over ensembles. Unless otherwise noted, a symmetric channel can be assumed as in Equation 62 below.

[1030] [Mathematical Formula 62]

[1031]

[1032] In this case, each element of matrix H can be separated into LoS ​​and NLoS components, each of which may exhibit distinct statistical properties. The following explanation is based on a Rician model that expresses these LoS and NLoS components additively. Accordingly, channel XPDs for the LoS and NLoS components can be defined individually, and the total channel XPD can be defined in terms of the effective channel XPD. In this context, this Rician model can be referred to as a generalized formulation that encompasses the AWGN and Rayleigh models.

[1033] Channel XPD is partly attributed to antenna impairments, which can cause cross-polarization leakage in radio signals. In real-world environments, polarized waves passing through antennas exhibit some degree of mixing, whereas ideal antennas can guarantee perfect isolation. The degree of this leakage (or isolation) can be measured in terms of antenna XPD.

[1034] These effects can occur in both transmitting and receiving antennas. Therefore, the antenna XPDs for the transmitting antenna and the receiving antenna are respectively XPD Tx Ant and XPD Rx Ant It can be defined individually and can be expressed commonly as in Equation 63 below.

[1035] [Mathematical Formula 63]

[1036]

[1037] In this case, antenna XPD relates to the input / output characteristics of individual antennas, whereas channel XPD can characterize the entire channel including the contribution of antenna XPD.

[1038] Wave reflections occurring during the propagation of radio waves through the air can be accompanied by polarization conversion. These scatterers can result in an unexpected increase in channel XPD. This random effect can be parameterized in terms of the expected amount of polarization shift, which can be determined statistically. This modeling is applied only to the NLoS channel component, as the LoS component is not accompanied by signal bouncing.

[1039] Unless otherwise noted, the statistical properties of polarization transformation can be assumed to be symmetric between the two polarization orientations.

[1040] Channel modeling for ATSC 3.0 MIMO systems that reflects polarization interactions caused by antenna characteristics and physical factors observed in the field, an understanding of the underlying factors related thereto, and an evaluation of channel XPD derived from these factors can be described.

[1041] In this case, the channel XPD may refer to the XPD defined at the input and output of MIMO channels in an inclusive context that encompasses contributions from fading and antenna. If the channel contains both LoS and NLoS components, a channel XPD specialized for each of these channel components can be defined individually.

[1042] In this case, the antenna XPD may refer to the XPD defined at the input and output of an individual antenna.

[1043] In this case, the effective channel XPD may refer to a channel XPD that explicitly represents the value measured across the entire channel by combining the contributions of the LoS component and the NLoS component.

[1044] At this time, XPD L It can represent the dB scale of the channel XPD evaluated in the LoS part of the MIMO channel.

[1045] At this time, XPD N It can represent the dB scale of the channel XPD evaluated in the NLoS part of the MIMO channel.

[1046] At this time, XPD eff It can represent the effective channel XPD on a dB scale.

[1047] At this time, XPD Tx Ant It can represent the antenna XPD on a dB scale measured at the transmitting antenna.

[1048] At this time, XPD Rx Ant It can represent the antenna XPD on a dB scale measured at the receiving antenna.

[1049] At this time, χ LoS is XPD L It can be a linear scale representation of. That is, it can be expressed as in Equation 64 below.

[1050] [Mathematical Formula 64]

[1051]

[1052] At this time, χ NLoS is XPD NIt can be a linear scale representation of. That is, it can be expressed as in Equation 65 below.

[1053] [Mathematical Formula 65]

[1054]

[1055] At this time, χ eff is XPD eff It can be a linear scale representation of. That is, it can be expressed as in Equation 66 below.

[1056] [Mathematical Formula 66]

[1057]

[1058] At this time, e T can represent the relative level of cross-polarization leakage compared to co-polarization signal power within the radiation output of the transmit antenna. This value is XPD Tx Ant It is determined by and expressed on a linear scale.

[1059] At this time, e R can represent the relative level of cross-polarization leakage compared to co-polarization signal power within the radiation output of the receiving antenna. This value is XPD Rx Ant It is determined by and expressed on a linear scale.

[1060] In this case, r ∈ [0, 1] can represent the fraction of polarization-shifted signal power within the reflected signal waves.

[1061] At this time, ρ L ∈ [0, 1] may be a parameter representing the power distribution between co- and cross-polarization components in the LoS part of the channel model. This value is XPD L It can be determined by.

[1062] At this time, ρ N ∈ [0, 1] may be a parameter representing the power distribution between co- and cross-polarization components in the NLoS part of the channel model. This value is XPD N It can be determined by.

[1063] In this case, K can be a Rician K-factor.

[1064] The aforementioned XPD Tx Ant and XPD Rx Ant This can be applied to the model as shown in the following mathematical formula 67.

[1065] [Mathematical Formula 67]

[1066]

[1067] At this time, e R and e Tcan reflect cross-polarization leakage in antennas and can be expressed as in the following mathematical equations 68 and 69, respectively.

[1068] [Mathematical Formula 68]

[1069]

[1070] [Mathematical Formula 69]

[1071]

[1072] At this time, A L and A N can be scaling factors that normalize and weight LoS and NLoS contributions. These parameters A L and A N Since it is implicitly accounted for in the Rician K-factor within the final model formulation, it may not be necessary to specify it separately.

[1073] At this time, H L O and H N O can represent the primitive forms of LoS and NLoS components, and can be expressed as in the following mathematical formulas 70 and 71, respectively.

[1074] [Mathematical Formula 70]

[1075]

[1076] [Mathematical Formula 71]

[1077]

[1078] The propagation fading terms G of the above mathematical equations 70 and 71 LoS and G NLoS It can be expressed as in the following mathematical formulas 72 and 73.

[1079] [Mathematical Formula 72]

[1080]

[1081] [Mathematical Formula 73]

[1082]

[1083] At this time, g 00 N , g 10 N , g 01 N and g 11 N 은 G NLoS The normalized random fading gain that applies to each entry of G NLoS They represent ) and can be iid complex Gaussian random variables with a mean of 0 and a variance of 1.

[1084] Through abstraction and normalization, the channel model can be expressed as shown in Equation 74 below.

[1085] [Mathematical Formula 74]

[1086]

[1087] At this time, the above mathematical formula 74 corresponds to the above mathematical formula 9.

[1088] At this time, in the above mathematical formula 74, the LoS component (H AWGN ) and NLoS components (H RL ) are as expressed in the above mathematical formulas 8 and 9, respectively.

[1089] At this time, g 00 , g 10 , g 01 and g 11 H RL The normalized random fading gain that applies to each entry of H RLThey represent ) and can be iid complex Gaussian random variables with a mean of 0 and a variance of 1.

[1090] At this time, ρ L and ρ N is e T , e R and can be determined by r and can be expressed as in Equation 75 below. These can be used on behalf of channel XPD values.

[1091] [Mathematical Formula 75]

[1092]

[1093] At this time, the channel XPD values ​​can be expressed as in the following mathematical formulas 76 and 77.

[1094] [Mathematical Formula 76]

[1095]

[1096] [Mathematical Formula 77]

[1097]

[1098] In this case, the above mathematical formula 76 is XPD L = 10log 10 χ LoS It is a linear scale representation of, and the above mathematical formula 77 is XPD N = 10log 10 χ NLoS It can be a linear scale representation of.

[1099] At this time, χ LoS and χ NLoS The effective channel XPD combined with can be expressed as shown in Equation 78 below.

[1100] [Mathematical Formula 78]

[1101]

[1102] Its dB scale representation is XPD eff = 10log 10 χ effIt can be given as follows.

[1103] In this case, the effective channel XPD is a value likely to be measured by actual field receivers. Since most receivers cannot distinguish the contribution of LoS and NLoS components, XPD L and XPD N Measurement capability may be limited to the comprehensive value of the effective channel XPD rather than a detailed evaluation of it.

[1104] An AWGN channel can represent a special case where K -> ∞. Since no NLoS signal exists in an AWGN channel, accordingly G NLoS becomes 0. In this case, the effective channel XPD matches the XPD evaluated in the LoS portion, i.e., χ eff = χ LoS It becomes. In this case, the effective channel XPD across the entire channel component can be a deterministic value controlled by the characteristics of the transmitting and receiving antennas.

[1105] Rayleigh channels can represent a special case where K = 0. Since there is no LoS ​​signal in Rayleigh channels, accordingly G LoS becomes 0. In this case, the effective channel XPD matches the XPD evaluated in the NLoS portion, i.e., χ eff = χ NLoS ... In this case, in addition to antenna properties, an uncontrollable environmental factor r can affect the effective channel XPD.

[1106] According to field observations, channel asymmetry can be observed, where XPDs differ between polarizations. This asymmetry can be attributed primarily to physical reactions during the radio wave reflection process. In other words, the degree of energy loss and polarization conversion may not be the same between horizontal and vertical polarizations, and this can also vary depending on the orientation of the reflection surface.

[1107] To accommodate this generalization, the NLoS channel component can be adjusted as shown in Equation 79 below.

[1108] [Mathematical Formula 79]

[1109]

[1110] At this time, b G ∈ [0, 1] may represent the relative weight of energy from polarization #1 retained after reflections compared to that of polarization #2.

[1111] In this case, r0 can represent the ratio of the signal power converted from polarization #1 to polarization #2 to the total reflected signal power originating from polarization #1 incidence.

[1112] In this case, r1 can represent the ratio of the signal power converted from polarization #2 to polarization #1 to the total reflected signal power originating from polarization #2 incidence.

[1113] In this generalized model, XPD N and XPD eff It can be defined separately depending on the polarization direction being measured. XPD measured at polarization #1 and polarization #2 N The values ​​are XPD N (0) and XPD N It can be represented as (1). In this case, XPD N (0) = 10log 10 χ NLoS (0) and XPD N (1) = 10log 10 χ NLoS (1) It can be.

[1114] At this time, χ NLoS (0) can be expressed as in the following mathematical formula 80, and χ NLoS (1) can be expressed as shown in the following mathematical formula 81.

[1115] [Mathematical Formula 80]

[1116]

[1117] [Mathematical Formula 81]

[1118]

[1119] The effective channel XPD values ​​measured at polarization #1 and polarization #2 are XPD eff (0) and XPD eff It can be represented as (1). In this case, XPD eff (0) = 10log 10 χeff (0) and XPD eff (1) = 10log 10 χ eff (1) It can be.

[1120] At this time, χ eff (0) can be expressed as in the following mathematical formula 82, and χ eff (1) can be expressed as shown in the following mathematical formula 83.

[1121] [Mathematical Formula 82]

[1122]

[1123] [Mathematical Formula 83]

[1124]

[1125] H in the above mathematical equation 74 characterizing the entire channel RL It can be modified as shown in the following mathematical formula 84.

[1126] [Mathematical Formula 84]

[1127]

[1128] At this time, H AWGN It can remain the same as before.

[1129] At this time, ρ N (0) may represent the power portion of co- and cross-polarization components originated in polarization #1 signals, particularly in context of the NLoS part of the MIMO channel. This value is ρ N (0) = χ NLoS (0) / ( 1 + χ NLoS (0) ) It can be.

[1130] At this time, ρ N(1) can represent the power portion of co- and cross-polarization components originated in polarization #2 signals, particularly in context of the NLoS part of the MIMO channel. This value is ρ N (1) = χ NLoS (1) / ( 1 + χ NLoS (1) ) It can be.

[1131] At this time, b H ∈ [0, 1] may represent the relative weight of polarization #1's signal energy observed at the receiver, compared to that of polarization #2.

[1132] At this time, b H This can illustrate the potential power asymmetricity between signal waves received through different polarization orientations and can be expressed as shown in Equation 85 below.

[1133] [Mathematical Formula 85]

[1134] b H =

[1135]

[1136] Calculation examples are described below. In this example, the following set of parameters may be applied.

[1137] XPDTx Ant 26dB

[1138] XPD Rx Ant 26dB

[1139] r 0.1 ( = 10%)

[1140] Based on the given settings, model parameters can be calculated. In this case, the given XPD Tx Ant and XPD Rx Ant from e T and e R This can be calculated as follows.

[1141] e T = 10 -(26 / 10) = 2.5119 * 10 -3

[1142] e R = 10 -(26 / 10) = 2.5119 * 10 -3

[1143] The above e T , e R and from r χ LoS and χ NLoS Calculated as in the following mathematical formulas 86 and 87, χ LoS = 100.03 and χ NLoS = 8.1655 can be obtained.

[1144] [Mathematical Formula 86]

[1145]

[1146] [Mathematical Formula 87]

[1147]

[1148] At this time, XPD L = 10log 10 100.03 = 20dB and XPD N = 10log 10 8.1655 = 9.35dB.

[1149] When K = 10, effective channel XPD χeff 53.419 can be obtained by calculating as in the following mathematical formula 88.

[1150] [Mathematical Formula 88]

[1151]

[1152] At this time, XPD eff = 10log 10 53.419 = 17.28dB.

[1153] When K approaches infinity (AWGN channel), the effective channel XPD can be calculated as follows.

[1154] χ eff 100.03

[1155] XPD eff 20dB

[1156] When K is 0 (Rayleigh channel), the effective channel XPD can be calculated as follows.

[1157] χ eff 8.1655

[1158] XPD eff 9.35dB

[1159] χ LoS and χ NLoS ρ calculated as follows according to L and ρ N This H AWGN and H RL Can decide.

[1160] ρ L = 100.03 / (1 + 100.03) = 0.9901

[1161] ρ N = 8.1655 / (1 + 8.1655) = 0.8960

[1162] In combination with K, the entire channel model H can be determined as shown in Equation 74 above.

[1163] FIG. 27 is an operation flowchart illustrating an example of a method for estimating the performance of a MIMO system according to an embodiment of the present invention.

[1164] Referring to FIG. 27, a method for estimating the performance of a MIMO system according to an embodiment of the present invention generates input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information (S2710).

[1165] In addition, a method for estimating the performance of a MIMO system according to an embodiment of the present invention generates a MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the channel condition information and cross-channel distinction information (S2720).

[1166] At this time, the MIMO required performance can be generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the channel condition information and the cross-channel distinction information.

[1167] At this time, the correction input value is input into a correction offset function, and the output of the correction offset function can correspond to the MIMO required performance.

[1168] At this time, the correction offset function may vary depending on the channel condition information.

[1169] At this time, the correction offset function may vary depending on the cross-channel distinction information.

[1170] At this time, the MIMO system is a first-type layered MIMO system, and the MIMO required performance may include one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer.

[1171] At this time, the core layer MIMO required performance and the enhanced layer MIMO required performance can be generated based on the injection level.

[1172] At this time, the performance of the MIMO system can be estimated using either a first mode corresponding to error-free complete channel estimation or a second mode corresponding to error-prone channel estimation.

[1173] At this time, the input information may further include pilot boosting information and pilot separation information in the second mode.

[1174] In addition, a method for estimating the performance of a MIMO system according to an embodiment of the present invention generates a system output based on the MIMO required performance (S2730).

[1175] For example, the system output may be an image in the form of a map drawn based on MIMO performance requirements. For example, the system output may be the result of performing a specific function based on MIMO performance requirements.

[1176] FIG. 28 is an operation flowchart illustrating an example of a method for estimating the coverage of a MIMO system according to an embodiment of the present invention.

[1177] Referring to FIG. 28, a method for estimating the coverage of a MIMO system according to an embodiment of the present invention generates input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information (S2810).

[1178] In addition, a method for estimating the coverage of a MIMO system according to an embodiment of the present invention generates a MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the channel condition information and cross-channel distinction information (S2820).

[1179] At this time, the MIMO required performance can be generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the channel condition information and the cross-channel distinction information.

[1180] At this time, the correction input value is input into a correction offset function, and the output of the correction offset function can correspond to the MIMO required performance.

[1181] At this time, the correction offset function may vary depending on the channel condition information.

[1182] At this time, the correction offset function may vary depending on the cross-channel distinction information.

[1183] At this time, the MIMO system is a first-type layered MIMO system, and the MIMO required performance may include one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer.

[1184] At this time, the core layer MIMO required performance and the enhanced layer MIMO required performance can be generated based on the injection level.

[1185] At this time, the performance of the MIMO system can be estimated using either a first mode corresponding to error-free complete channel estimation or a second mode corresponding to error-prone channel estimation.

[1186] At this time, the input information may further include pilot boosting information and pilot separation information in the second mode.

[1187] In addition, a method for estimating the coverage of a MIMO system according to an embodiment of the present invention generates a coverage output based on the result of comparing the MIMO required performance with a comparison target performance corresponding to a specific location (S2830).

[1188] For example, the coverage output may be an image output that plots the estimated coverage on a map. In this case, the coverage can be estimated by comparing the required signal quality (MIMO required performance) of the point with a measured or predicted value of the received signal quality. In this case, if the required signal quality is the required CNR, an area including points having a CNR measured value or CNR predicted value higher than the required CNR may be depicted as the area covered by the MIMO broadcast signal.

[1189]

[1190] As described above, the broadcast signal transmission device, method, broadcast signal reception method, device and method for estimating the performance of a MIMO system, device and method for estimating the coverage of a MIMO system according to the present invention are not limited to the configurations and methods of the embodiments described above; rather, all or part of each embodiment may be selectively combined to allow for various modifications to be made to the embodiments.

Claims

An input processing unit that generates input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information; A MIMO (Multiple Input Multiple Output) required performance estimation unit that generates MIMO required performance from the SISO required performance using the above channel condition information and cross-channel distinction information; and A device for estimating the performance of a MIMO system, comprising an output interface unit that generates a system output based on the above-mentioned MIMO required performance. In claim 1, The above MIMO required performance is A device for estimating the performance of a MIMO system, generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the above channel condition information and the above cross-channel distinction information. In claim 2, The above correction input value is A device for estimating the performance of a MIMO system, which is input to a correction offset function, and whose output corresponds to the required MIMO performance. In claim 3, The above correction offset function is A device for estimating the performance of a MIMO system that varies according to the above channel condition information. In claim 4, The above correction offset function is A device for estimating the performance of a MIMO system that varies according to the above cross-channel distinction information. In claim 4, The above MIMO system is a first-type layered MIMO system, and A device for estimating the performance of a MIMO system, wherein the above-mentioned MIMO required performance includes one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer. In claim 6, A device for estimating the performance of a MIMO system, wherein the core layer MIMO required performance and enhanced layer MIMO required performance are generated based on the injection level. In claim 3, The above MIMO required performance is A device for estimating the performance of a MIMO system, which is estimated using either a first mode corresponding to error-free complete channel estimation or a second mode corresponding to error-prone channel estimation. In claim 8, The above input information An apparatus for estimating the performance of a MIMO system, further comprising pilot boosting information and pilot separation information in the second mode. A step of generating input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information; A step of generating MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the above channel condition information and cross-channel distinction information; and A method for estimating the performance of a MIMO system, comprising the step of generating a system output based on the above-mentioned MIMO required performance. In claim 10, The above MIMO required performance is A method for estimating the performance of a MIMO system, generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the above channel condition information and the above cross-channel distinction information. In claim 11, The above correction input value is A method for estimating the performance of a MIMO system, wherein the input to a correction offset function and the output of the correction offset function corresponds to the required MIMO performance. In claim 12, The above correction offset function is A method for estimating the performance of a MIMO system that varies according to the above channel condition information. In claim 13, The above correction offset function is A method for estimating the performance of a MIMO system that varies according to the above cross-channel distinction information. In claim 13, The above MIMO system is a first-type layered MIMO system, and A method for estimating the performance of a MIMO system, wherein the above-mentioned MIMO required performance includes one or more of the core layer MIMO required performance for the core layer and the enhanced layer MIMO required performance for the enhanced layer. In claim 15, A method for estimating the performance of a MIMO system, wherein the core layer MIMO required performance and enhanced layer MIMO required performance are generated based on the injection level. In claim 12, The above MIMO required performance is A method for estimating the performance of a MIMO system, which is estimated using either a first mode corresponding to an error-free complete channel estimation or a second mode corresponding to an error-prone channel estimation. In claim 17, The above input information A method for estimating the performance of a MIMO system, further comprising pilot boosting information and pilot separation information in the second mode above. A step of generating input information including SISO (Single Input Single Output) required performance, channel condition information, and cross-channel discrimination information; A step of generating MIMO (Multiple Input Multiple Output) required performance from the SISO required performance using the above channel condition information and cross-channel distinction information; and A method for estimating the coverage of a MIMO system, comprising the step of generating a coverage output based on the result of comparing the above-mentioned MIMO required performance with a comparison target performance corresponding to a specific location. In claim 19, The above MIMO required performance is A method for estimating the coverage of a MIMO system, generated by correcting a correction input corresponding to an intermediate estimate generated based on one or more of the above channel condition information and the above cross-channel distinction information.

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