Compensation method, acquisition method and acquisition system with interleaved data acquisition

Abstract

The present invention relates to a compensation method, an acquisition method and an acquisition system with interleaved data acquisition, wherein the compensation method calculates the time delay and phase offset of the second channel based on the spectral line steps of the overlapping frequency bands of the two signals of the first channel and the second channel and compensates for the phase difference in the overlapping frequency bands of the two signals. The present invention can effectively eliminate the time delay and phase offset by calculating the time delay and phase offset of the second channel and compensating for the phase difference in the overlapping frequency bands of the two signals without the need for pilot tones or additional hardware, while avoiding problems such as changes in the original input signal caused by nonlinear group delay. It can also be applied to signals with partially overlapping frequencies to detect linear phase misalignment.

Description

Technical Field

[0001] The invention relates to the field of data acquisition, and in particular to a compensation method, an acquisition method and an acquisition system with interleaved data acquisition. Background Art

[0002] In order to keep up with the changes in the frequency of signal explosion in electronic systems, the bandwidth of data acquisition systems (DAS) in electronic devices such as communication receivers and electronic instruments is as high as tens or even hundreds of GHz. As a core device, the analog-to-digital converter (ADC) in the acquisition system greatly defines the upper limit of the DAS bandwidth. In the foreseeable future, the improvement nodes of the upcoming complementary metal oxide semiconductor (CMOS) ADC cannot adapt to the expected bandwidth requirements of the next generation of DAS. To solve this contradiction, parallel DAS architectures such as band interleaved (BI) DAS, frequency interleaved (FI) DAS and asynchronous time interleaved (ATI) DAS are attractive solutions that go beyond the limitations of traditional CMOS ADC devices.

[0003] These parallel DAS architectures have similar strategies, transferring high-frequency signals to baseband and recovering the signals in the digital backend after sampling with a low-bandwidth ADC. Taking BI-DAS as an example, BI-DAS divides the frequency of the broadband signal into multiple narrow sub-bands through analog filters, and transfers the high-frequency sub-bands to low-frequency sub-bands through analog down-conversion, thereby reducing the bandwidth pressure of the ADC. After the ADC quantizes the signals of each sub-band, the signals of each sub-band are converted back to the original frequency band through digital signal processing. After that, the signals of multiple frequency bands are merged in the digital domain to recover the original signal.

[0004] However, due to the transition region of the analog filter, the signal of a particular frequency band may appear in two adjacent sub-bands at the same time, which is called overlapping frequency. The phase misalignment (PM) between the two sub-bands in the overlapping frequency band may cause these signals to cancel each other or partially cancel each other when the sub-signals are combined. The resulting combined frequency response may accordingly have an undesirable attenuated amplitude response in the overlapping frequency band.

[0005] There is a great need for a method or system to analyze overlapping frequency bands to eliminate time delay and phase offset. Summary of the invention

[0006] The purpose of the present invention is to overcome the shortcomings of the prior art and provide a compensation method, an acquisition method and an acquisition system with interleaved data acquisition, which can effectively eliminate time delay and phase offset without the need for pilot tone or additional hardware, while avoiding problems such as changes in the original input signal caused by nonlinear group delay.

[0007] The objective of the present invention is achieved through the following technical solutions:

[0008] A compensation method with interleaved data acquisition is disclosed. The compensation method calculates the time delay and phase offset of the second channel based on the spectral line steps of the overlapping frequency bands of the two signals of the first channel and the second channel and compensates for them to align the phase difference in the overlapping frequency bands of the two signals.

[0009] Furthermore, the spectral line steps of the overlapping frequency bands of the two signals are determined by the phase difference coefficient m express.

[0010] Furthermore, the phase difference coefficient m It is calculated based on three strongly correlated line spectrum sampling points with high signal-to-noise ratio found in the overlapping frequency band of the phase spectra of the first channel and the second channel;

[0011] The phase difference coefficient m The calculation formula is: ; In the formula, z 1. z 2 and z 3 represent the slopes at the first, second and third sampling points of the three strongly correlated line spectra respectively; , and Respectively represent the phase difference differentials at the first, second and third sampling points of the three strongly correlated line spectra;

[0012] The calculation formula for the time delay of the second channel is: ; In the formula, represents the time delay of the second channel, N Indicates the number of spectral lines;

[0013] The calculation formula for the phase offset of the second channel is: ; In the formula, Indicates the phase offset of the second channel.

[0014] Further, the first point and the second point of the three strongly correlated line spectra are located at two ends of a step in an overlapping region of the phase-frequency diagrams of the two signals.

[0015] Further, the signal-to-noise ratio calculation formula is: ; In the formula, Indicates frequency, express The signal-to-noise ratio of the frequency band, and Respectively The self-spectrum of the first and second channels of the frequency band, express Cross spectrum of the first and second channels of the frequency band.

[0016] A collection method with interlaced data collection, applying the above-mentioned compensation method with interlaced data collection; comprising the following steps:

[0017] (1) The first channel performs low-pass filtering on the input signal, and the second channel performs band-pass filtering on the input signal;

[0018] (2) calculating the time delay and phase shift of the second channel and performing delay and phase shift compensation on the signal of the second channel accordingly;

[0019] (3) Down-converting the signal of the second channel to baseband;

[0020] (4) performing analog-to-digital conversion on the signals of the first channel and the second channel;

[0021] (5) Up-converting the signal of the second channel to its original frequency band;

[0022] (6) Add the signals of the first channel and the second channel to obtain a digital output signal.

[0023] A collection system with interleaved data collection, applying the above-mentioned collection method with interleaved data collection, comprises a signal input end, a low-pass filter, a band-pass filter, a compensation circuit, an analog oscillator, a first analog-to-digital converter, a second analog-to-digital converter, a digital oscillator, an adder and a signal output end, wherein the signal input end is electrically connected to the low-pass filter and the band-pass filter respectively, the other end of the low-pass filter is electrically connected to the first analog-to-digital converter, the other end of the band-pass filter is serially connected to the compensation circuit, the analog oscillator, the second analog-to-digital converter and the digital oscillator in sequence, the first analog-to-digital converter and the digital oscillator are both electrically connected to the input end of the adder, and the output end of the adder is electrically connected to the signal output end.

[0024] Furthermore, the characteristic frequency value of the analog oscillator is greater than the upper cutoff frequency of the bandpass filter.

[0025] Furthermore, the analog oscillator is an analog local oscillator; and the digital oscillator is a digital local oscillator.

[0026] Furthermore, the compensation circuit includes a delay device and a phase shifter connected in series.

[0027] The beneficial effects of the present invention are:

[0028] The present invention aligns the phase difference in the overlapping frequency band of two signals by calculating the time delay and phase offset of the second channel and compensating for them, which can effectively eliminate the time delay and phase offset without the need for pilot tone or additional hardware, while avoiding problems such as changes in the original input signal caused by nonlinear group delay. It can also be applied to signals with partially overlapping frequencies to detect linear phase misalignment. BRIEF DESCRIPTION OF THE DRAWINGS

[0029] Figure 1 Schematic diagram for splitting a broadband input signal into two band-limited channels;

[0030] Figure 2 G with overlapping area x1 and G x2 Schematic diagram of the amplitude-frequency response;

[0031] Figure 3 is the phase difference between the two signals in the overlapping frequency range Schematic diagram of

[0032] Figure 4 It is a block diagram of the dual-channel system of the present invention. DETAILED DESCRIPTION

[0033] The following describes the embodiments of the present invention by specific examples, and those skilled in the art can easily understand other advantages and effects of the present invention from the contents disclosed in this specification. The present invention can also be implemented or applied through other different specific embodiments, and the details in this specification can also be modified or changed in various ways based on different viewpoints and applications without departing from the spirit of the present invention. It should be noted that the following embodiments and features in the embodiments can be combined with each other without conflict.

[0034] It should be noted that the illustrations provided in the following embodiments are only schematic illustrations of the basic concept of the present invention, and thus the drawings only show components related to the present invention rather than being drawn according to the number, shape and size of components in actual implementation. In actual implementation, the type, quantity and proportion of each component may be changed arbitrarily, and the component layout may also be more complicated.

[0035] Embodiment 1:

[0036] Figure 1 As shown, a dual-channel system will have a system estimate of linear phase alignment (time delay) by splitting a broadband input signal into two band-limited channels. and phase shift ) problem.

[0037] like Figure 2 As shown in , there is a certain degree of overlapping frequency region between two adjacent sub-bands, and the middle area represents the intersection of the two sub-bands. a and ω b The signal between the two sub-bands will appear in both sub-bands at the same time. Due to the transition band of the first sub-band, the signal of this frequency is not sufficiently attenuated in the first sub-band, so that part of the signal still enters the first sub-band. Therefore, when the signals are combined in the digital domain, the PM between the two sub-bands in this frequency may cause the signals to cancel each other or partially cancel each other.

[0038] The core of this embodiment is to estimate the linear phase misalignment, and its alignment method is based on two overlapping frequency band diagrams ( Figure 3 ), if the frequencies of the two channels overlap in a certain frequency range, the time delay can be estimated based on the gradient (i.e. slope) and intercept of the phase difference in the overlapping frequency band ( ) and phase shift ( ). Therefore, this approach allows for simultaneous and consistent estimation of and .

[0039] The output of the first and second channels of a two-channel system is modeled as:

[0040] {x}_{1}\left [ {n} \right ]={x}_{1}\left ( {n{T}_{s}} \right )+{n}_{1}\left [ {n} \right ] ,

[0041] {x}_{2}\left [ {n} \right ]={x}_{2}\left ( {n{T}_{s}-δ} \right )\times {e}^{-jφ}+{n}_{2}\left [ {n} \right ] ;

[0042] In the formula and denote time delay and phase shift respectively; n 1[ n ]and n 2[ n ] represent the noise in the first channel and the second channel respectively, T s represents the sampling period, which must be higher than the Nyquist rate of the measured signal, nT s In n represents the sampling number or time point of the signal. In addition, suppose that the two signals n 1[ n ]and n 2[ n ] are uncorrelated with each other.

[0043] The cross spectrum of the two channel signals is defined as {Gx}_{1}{x}_{2}\left [ {ω} \right ]={X}_{1}\left [ {ω} \right ]{X}^{*}_{2}\left [ {ω} \right ] , * represents the conjugation operator symbol.

[0044] In the formula, Indicates frequency, Indicates that a single channel is self-spectral ( x = x 1 or x 2), For the first channel: {Gx}_{1}{x}_{1}\left [ {ω} \right ]={X}_{1}\left [ {ω} \right ]{X}^{*}_{1}\left [ {ω} \right ] ; For the second channel: {Gx}_{2}{x}_{2}\left [ {ω} \right ]={X}_{2}\left [ {ω} \right ]{X}^{*}_{2}\left [ {ω} \right ] . Indicates noise n 1 and n 2, {Gn}_{1}{n}_{2}\left [ {ω} \right ]={n}_{1}\left [ {ω} \right ]{n}^{*}_{2}\left [ {ω} \right ] ; is zero in the case of uncorrelated noise. It is assumed that the cross spectrum between each input signal and its noise is uncorrelated.

[0045] The phase difference between the two channel signals It is expressed as:

[0046] Phase Difference It is N Spectral lines and gradients A linear function of . Figure 3 , time delay The phase offset is estimated based on the slope of the phase difference data. According to the intercept of the phase difference axis, the two parameters in the figure are estimated. , Respectively , The estimated value of .

[0047] Based on the above situation, a compensation method, an acquisition method and an acquisition system with interleaved data acquisition are proposed.

[0048] like Figures 1 to 4As shown, a compensation method with interleaved data acquisition is provided, wherein the compensation method calculates the time delay and phase offset of the second channel based on the spectral line steps of the two signals in the overlapping frequency band of the two signals of the first channel and the second channel and compensates for them to align the phase difference in the overlapping frequency band of the two signals.

[0049] The values ​​of time delay and phase offset are calculated based on the spectral line steps caused by signal aliasing in the overlapping region of the two channels in the phase-frequency characteristic spectrum. A compensation method with interleaved data acquisition uses the information contained in the overlapping frequency band to align the two signals, thereby effectively compensating for the difference between the two channel signals; specifically, by using the estimated gradient to compensate for the time delay and phase offset in the second channel signal.

[0050] The spectral line steps of the overlapping frequency bands of the two signals are divided by the phase difference coefficient m express.

[0051] The spectral line step is calculated by calculating the phase difference coefficient m Indicates the step size, thus reflecting the degree of phase mismatch between the two channels.

[0052] The mismatch between the two channel phases (i.e. the phase difference between the two channel signals) ) is specifically expressed as a time delay and phase shift The linear relationship ( is the frequency, N is the number of spectral lines):

[0053]

[0054] The phase difference coefficient m It is calculated based on three strongly correlated line spectrum sampling points with high signal-to-noise ratio found in the overlapping frequency band of the phase spectra of the first channel and the second channel;

[0055] The phase difference coefficient m The calculation formula is:

[0056]

[0057] In the formula, z 1. z 2 and z 3 represent the slopes at the first, second and third sampling points of the three strongly correlated line spectra respectively; , and Respectively represent the phase difference differentials at the first, second and third sampling points of the three strongly correlated line spectra;

[0058] The calculation formula for the time delay of the second channel is:

[0059] ;

[0060] In the formula, represents the time delay of the second channel, N Indicates the number of spectral lines;

[0061] The calculation formula for the phase offset of the second channel is:

[0062]

[0063] In the formula, Indicates the phase offset of the second channel.

[0064] The signal-to-noise ratio calculation formula is:

[0065] ; In the formula, Indicates frequency, express The signal-to-noise ratio of the frequency band, and Respectively The self-spectrum of the first and second channels of the frequency band, express Cross spectrum of the first and second channels of the frequency band.

[0066] The signal-to-noise ratio calculation formula is established under the assumption that the random noise in the first channel and the second channel has the same distribution. The relationship between the sampling point signal-to-noise ratio (SNR) and the autospectrum (G x1x1 With G x2x2 ) and their cross spectrum (G x1x2 )related.

[0067] The selection of three sampling points in the overlapping region of the phase spectrum should be based on the principle that they all have strongly correlated line spectra with high signal-to-noise ratio.

[0068] That is, the calculation of the time delay and phase offset of the second channel includes the following steps:

[0069] S1: Find three strongly correlated line spectrum sampling points with high signal-to-noise ratio through the signal data of the first channel and the second channel;

[0070] The three strongly correlated line spectrum sampling points are expressed as ( , )、( , )and( , ).

[0071] S2: Calculate the phase difference coefficient based on three strongly correlated line spectra m；

[0072]

[0073] In the formula, z 1. z 2 and z 3 represent the slopes at the first, second and third sampling points of the three strongly correlated line spectra respectively; , and Respectively represent the phase difference differentials at the first, second and third sampling points of the three strongly correlated line spectra;

[0074] The first and second points of the three strongly correlated line spectra are located at both ends of the step in the overlapping region of the phase-frequency diagrams of the two signals.

[0075] The phase difference coefficient represents the phase step coefficient caused by time delay and phase error in the overlapping area.

[0076] S3: Calculate the time delay of the second channel :

[0077] ; In the formula, N Indicates the number of spectral lines;

[0078] Time delay of the second channel Phase difference coefficient m , and the coordinates of two sampling points at both ends of the step in the overlapping area of ​​the phase-frequency diagram.

[0079] S4: Calculate the phase offset of the second channel : ;

[0080] S5: According to the time delay of the second channel and phase shift The compensated electrical signal of the second channel can be calculated according to the following formula:

[0081] {X}_{2c}\left [ {ω} \right ]={e}^{j\frac {2π} {N}kδ+jφ}{X}_{2}\left [ {ω} \right ] ;

[0082] The invention discloses a compensation method with interleaved data acquisition, which is a dual-channel compensation method with interleaved data acquisition.

[0083] A collection method with interlaced data collection, applying the above-mentioned compensation method with interlaced data collection; comprising the following steps:

[0084] (1) The first channel performs low-pass filtering on the input signal, and the second channel performs band-pass filtering on the input signal;

[0085] (2) calculating the time delay and phase shift of the second channel and performing delay and phase shift compensation on the signal of the second channel accordingly;

[0086] (3) Down-converting the signal of the second channel to baseband;

[0087] The higher frequency band signal in the second channel is down-converted to baseband by an analog local oscillator, whose characteristic frequency value is expressed as Ω l ,Ω l It should be greater than the upper cutoff frequency of the bandpass filter to eliminate the low-frequency signal split off by the analog local oscillator and retain the high-frequency signal.

[0088] (4) performing analog-to-digital conversion on the signals of the first channel and the second channel;

[0089] (5) Up-converting the signal of the second channel to its original frequency band;

[0090] After the two channel signals pass through the first analog-to-digital converter and the second analog-to-digital converter respectively, the signal of the second channel is up-converted to its original frequency band through the digital local oscillator, and its frequency is represented by ω l .

[0091] (6) Add the signals of the first channel and the second channel to obtain a digital output signal.

[0092] This step obtains the digital output signal Y[n] after passing through the adder.

[0093] A collection system with interleaved data collection, applying the above-mentioned collection method with interleaved data collection, comprises a signal input end, a low-pass filter, a band-pass filter, a compensation circuit, an analog local oscillator, a first analog-to-digital converter, a second analog-to-digital converter, a digital local oscillator, an adder and a signal output end, wherein the signal input end is electrically connected to the low-pass filter and the band-pass filter respectively, the other end of the low-pass filter is electrically connected to the first analog-to-digital converter, the other end of the band-pass filter is serially connected to the compensation circuit, the analog local oscillator, the second analog-to-digital converter and the digital local oscillator in sequence, the first analog-to-digital converter and the digital local oscillator are both electrically connected to the input end of the adder, and the output end of the adder is electrically connected to the signal output end.

[0094] The characteristic frequency value of the analog local oscillator is greater than the upper cut-off frequency of the band-pass filter.

[0095] The compensation circuit includes a delay device and a phase shifter connected in series.

[0096] A compensation circuit is introduced in the second channel to eliminate the time delay and phase difference between the two channels.

[0097] The performance of the proposed method is evaluated by reconstructing RF pulses captured using a prototype of a two-channel system. If all filters are assumed to be ideal with zero group delay, the relative time delay and phase shift of the second channel with respect to the first channel are expressed as and Before the experimental measurement, and For uncertainties, measured values ​​are required.

[0098] First, the input pulse is split into two pulses using a power divider and then fed into two channels. The first channel captures the signal in the baseband (0, ω1) using an analog low-pass filter. The second channel captures the intermediate frequency signal through an analog bandpass filter in the frequency band (ω1, ω2). The frequency is f l The local oscillator of the DAC down-converts the filtered IF band signal to baseband. Finally, an analog low-pass filter removes unwanted images above ω2. The pulses from each input channel are digitized using an ADC evaluation board (NationalSemiconductor ADC08D1500 evaluation board, which contains dual 8-bit 1.5GSps ADCs).

[0099] The RF pulses were generated by gating a ω1 MHz sine wave. The resulting pulses were broadband signals consisting of distinct line spectra. Using a prototype board with the aforementioned setup, a sufficient number of samples of each ADC channel, greater than 2000, were captured to obtain the spectrum of the digitized signal. These sampled signals were used to reconstruct the RF pulses using Matlab.

[0100] Then, the phase difference and signal-to-noise ratio are measured. Since it is a linear phase, the phase difference points of the three points can approximately form a straight line, so the phase difference can be used to estimate and First, the compensation signal generation method of this embodiment is used to select three peaks with high signal-to-noise ratios; the signal-to-noise ratios of overlapping frequency bands. The signal-to-noise ratio with the highest value is found in the frequency of calculating the phase difference.

[0101] Finally, the second channel is compensated using the calculated time delay and phase offset. When no compensation method is used, reconstruction from the uncompensated signal will not produce satisfactory results due to the phase misalignment between the two channels. When both the time delay and phase offset are correctly compensated, an accurate reconstructed pulse can be obtained.

[0102] A compensation method, acquisition method and acquisition system with interleaved data acquisition can effectively eliminate time delay and phase offset without pilot tone or additional hardware by calculating the time delay and phase offset of the second channel and compensating for them to align the phase difference in the overlapping frequency band of two signals. It can also be applied to signals with partially overlapping frequencies to detect linear phase misalignment.

[0103] A data acquisition system with interleaved data acquisition is a circuit structure with interleaved data acquisition system (BI-DAS), which can eliminate the time delay and phase difference between two channels.

[0104] A compensation method with interleaved data acquisition, an acquisition method aligns the phase difference in the overlapping frequency band of two signals by using an algorithmically estimated gradient compensation for the time delay and phase offset in the second channel signal. Compared with other traditional methods, this method can align the two signals without the need for pilot tones or additional hardware, while avoiding problems such as changes to the original input signal caused by nonlinear group delay.

[0105] A compensation method with interleaved data acquisition, an acquisition method is a new method to align two signals using the information contained in the overlapping frequency bands. In particular, the phase difference in the overlapping frequency band of the two signals is aligned by compensating the time delay and phase offset in the second signal using the estimated gradient.

[0106] The time delay and phase shift are caused by the time delay difference, insertion loss and slow attenuation of the amplitude-frequency characteristic of the analog low-pass filter and band-pass filter of the frequency division function.

[0107] A compensation method with interleaved data acquisition, an acquisition method and an acquisition system are capable of performing time delay and phase offset cancellation simultaneously. This method does not require additional hardware. In addition, it can be applied to signals with partially overlapping frequencies to detect linear phase misalignment.

[0108] A new phase alignment method for a dual-channel system with partially overlapping spectra is provided. The method requires only three line spectra in the overlapping spectrum and does not require a pilot tone or any additional hardware to estimate the linear phase misalignment. The present method can avoid the following disadvantages of implementing conventional methods:

[0109] First, the traditional method first compensates for the delay caused by the difference in electrical path length, and second eliminates the phase shift at a specific frequency. This method introduces a nonlinear group delay problem in the system, which can seriously change the original input signal.

[0110] Second, since most multichannel system applications involve time domain measurements, a pilot tone must be inserted at a frequency outside the measurement band. Therefore, insertion and detection require a significant amount of additional hardware, including power dividers, power combiners, attenuators, bandpass filters, and pilot tones for frequency dividers. This hardware creates additional costs and maintenance issues.

[0111] Finally, delay compensation performed separately through hardware calibration using integer and fractional digital filters is inefficient because two different compensations are required for each measurement. Most importantly, separate delay and phase offset compensation methods may introduce errors because the two misalignment components may be correlated with each other.

[0112] The above-mentioned embodiments only express the specific implementation of the present invention, and the description thereof is relatively specific and detailed, but it cannot be understood as limiting the scope of the present invention. It should be pointed out that, for ordinary technicians in this field, several variations and improvements can be made without departing from the concept of the present invention, which all belong to the protection scope of the present invention.

Claims

1. A compensation method with interleaved data acquisition, characterized in that: The compensation method calculates the time delay and phase offset of the second channel based on the spectral line steps of the overlapping frequency bands of the two signals of the first channel and the second channel and compensates for them to align the phase difference in the overlapping frequency bands of the two signals; The spectral line steps of the overlapping frequency bands of the two signals are represented by a phase difference coefficient m; The phase difference coefficient m is calculated based on three strongly correlated line spectrum sampling points with high signal-to-noise ratio found in the overlapping frequency band of the phase spectra of the first channel and the second channel; The calculation formula of the phase difference coefficient m is: Wherein, z1, z2 and z3 represent the slopes at the first, second and third points of the three strongly correlated line spectrum sampling points, respectively; Δθ1, Δθ2 and Δθ3 represent the phase difference differentials at the first, second and third points of the three strongly correlated line spectrum sampling points, respectively; The calculation formula for the time delay of the second channel is: In the formula, δ represents the time delay of the second channel, and N represents the number of spectral lines; The calculation formula of the phase offset of the second channel is: Where φ represents the phase offset of the second channel.

2. A compensation method with interleaved data acquisition according to claim 1, characterized in that: The first point and the second point of the three strongly correlated line spectra are located at two ends of the step in the overlapping region of the phase-frequency diagrams of the two signals.

3. A compensation method with interleaved data acquisition according to claim 1, characterized in that: The signal-to-noise ratio calculation formula is: In the formula, ω represents the frequency, SNR[ω] represents the signal-to-noise ratio in the ω frequency band, and They represent the autospectra of the first and second channels of the ω band, It represents the cross spectrum between the first channel and the second channel in the ω band.

4. A collection method with interlaced data collection, using the compensation method with interlaced data collection according to claim 1, characterized in that: The following steps are involved: (1) The first channel performs low-pass filtering on the input signal, and the second channel performs band-pass filtering on the input signal; (2) calculating the time delay and phase shift of the second channel and performing delay and phase shift compensation on the signal of the second channel accordingly; (3) down-converting the signal of the second channel to baseband; (4) performing analog-to-digital conversion on signals of the first channel and the second channel; (5) up-converting the signal of the second channel to its original frequency band; (6) The signals of the first channel and the second channel are added to obtain a digital output signal.

5. A collection system with interleaved data collection, using the collection method with interleaved data collection as claimed in claim 4, characterized in that: The invention comprises a signal input terminal, a low-pass filter, a band-pass filter, a compensation circuit, an analog oscillator, a first analog-to-digital converter, a second analog-to-digital converter, a digital oscillator, an adder and a signal output terminal, wherein the signal input terminal is electrically connected to the low-pass filter and the band-pass filter respectively, the other end of the low-pass filter is electrically connected to the first analog-to-digital converter, the other end of the band-pass filter is connected in series with the compensation circuit, the analog oscillator, the second analog-to-digital converter and the digital oscillator in sequence, the first analog-to-digital converter and the digital oscillator are both electrically connected to the input terminal of the adder, and the output terminal of the adder is electrically connected to the signal output terminal.

6. The acquisition system with interleaved data acquisition according to claim 5, characterized in that: The characteristic frequency value of the analog oscillator is greater than the upper cut-off frequency of the band-pass filter.

7. The acquisition system with interleaved data acquisition according to claim 5, characterized in that: The analog oscillator is an analog local oscillator; the digital oscillator is a digital local oscillator.

8. The acquisition system with interleaved data acquisition according to claim 5, characterized in that: The compensation circuit includes a delay device and a phase shifter connected in series.

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