High-consistency sum-difference network structure and implementation method

Abstract

The invention discloses a high-consistency sum-difference network structure and an implementation method, and relates to the technical field of phased-array antennae, the high-consistency sum-difference network structure comprises a broadband sum-difference device part and a power divider assembly, and the sum-difference device part comprises four 3dB coupling bridges and four 90-degree broadband phase shifters matched with the corresponding 3dB coupling bridges; the four 3dB coupling bridges and the four 90-degree broadband phase shifters are matched to superpose and subtract input signals and output sum signals, x-difference signals, y-difference signals and double-difference signals at the same time, and the double-difference signals are absorbed and matched through buried resistors and short-circuit branches; and the power divider component performs power division or power combination on the sum signal, the x difference signal and the y difference signal, and outputs the sum signal, the x difference signal and the y difference signal to a next-stage component. According to the invention, the design is reasonable, and the broadband sum-difference network has good amplitude-phase consistency in the K wave band. The sum-difference beam forming network in the form has better processing consistency, the production and assembly difficulty is greatly reduced, and the production efficiency and the yield in the assembly process are improved.

Description

Technical Field

[0001] The present invention relates to the technical field of phased array antennas, and more specifically to the technical field of a high consistency and difference network structure and an implementation method thereof. Background Art

[0002] With the rapid development of mobile communications, satellite communications and satellite-borne electronics, the requirements for system capacity are getting higher and higher. Due to the extremely rich spectrum resources in the high-frequency microwave band, modern communication systems are developing towards high-frequency microwaves, especially millimeter wave bands.

[0003] Phased array antennas, also known as electronically scanned antennas or electronically scanned array antennas, are developed from the array antennas used in the early days. Because the beam pointing and beam shape of phased array antennas have the ability to change rapidly, compared with ordinary array antennas or parabolic antennas, the performance of phased array systems can be greatly improved, making it easier to realize more system functions and enabling the system and equipment to have stronger adaptability when the working environment and observation targets change.

[0004] As a representative technological breakthrough, the millimeter wave phased array system realizes the directional transmission of large-bandwidth millimeter wave signals by controlling the phase of the input signal in the large-scale antenna array, solving the problem of large path loss of millimeter wave signals. The development of this technology has made millimeter wave phased array systems widely used in both military and civilian fields. For the phased array direction finding problem, the single pulse method is the most widely used.

[0005] Single pulse angle measurement technology is a very mature and accurate angle measurement method. It not only has the advantages of small amount of calculation, simplicity and reliability, but more importantly, it has a high data rate and strong anti-interference ability. In theory, single pulse angle measurement only needs to analyze one echo to extract the angle error information (the angle of the target deviating from the beam center). Therefore, it is not only used in tracking radars to achieve precise tracking and measurement of targets, but also in various search radars to improve the angle measurement accuracy. It is also widely used in communications, radio astronomy, sonar and optical tracking.

[0006] Early single pulse angle measurement methods include amplitude comparison, phase comparison, and sum-difference comparison. Amplitude comparison refers to the phased array antenna feed system forming two beams with slightly offset directions but both covering the radar angle measurement area. The two beams receive echo signals and transmit them to the signal processor through their respective receiving channels. By comparing the amplitudes of the output signals of the two channels, the precise location of the target can be determined. Phase comparison method refers to the phased array antenna feed system forming two receiving beams with the same shape and direction, but different phase centers in height. The upper and lower receiving beams cover the same airspace in space, and the position of the target can be obtained by measuring the phase difference between the two receiving beam signals. The sum-difference comparison method is to obtain the angle information of the target deviating from the beam direction by comparing the difference and ratio of the sum-difference beam receiving signals. Compared with amplitude comparison and phase comparison, the sum-difference comparison single pulse angle measurement method does not require the beam to be fully symmetrical about the central beam axis, which reduces the source of angle measurement error. It is simple and effective, with small amount of calculation, and is widely used in many fields. At this stage, there is no specific classification of single pulse comparison methods, and the form of sum-difference comparison is generally adopted.

[0007] The main components of the millimeter wave phased array antenna with angle measurement function are: antenna array, TR transceiver components, sum and difference beamforming network, beam controller, antenna interface unit and power module, etc. The sum and difference network is the core system for single pulse technology to realize beam tracking function.

[0008] Traditional summators and differential devices are constructed using a magic-T structure or microstrip lines. The magic-T structure is too large, and the design and processing are difficult and costly, making it unsuitable for airborne platforms; traditional microstrip line summators and differential devices are composed of a 3dB coupling bridge and a 90° microstrip delay line. The 90° microstrip delay line uses the length of the microstrip line to achieve phase shift, and is a narrowband structure with poor flatness within the band, which ultimately affects the consistency of the entire summator and differential network. At the same time, the microstrip line structure has high assembly requirements, and it is difficult to ensure high assembly consistency between finished products. Summary of the invention

[0009] The purpose of the present invention is to solve the technical problem that the traditional microstrip line sum-difference device is composed of a 3dB coupling bridge and a 90° microstrip delay line, which affects the amplitude and phase consistency and assembly consistency of the entire sum-difference network. The present invention provides a high-consistency sum-difference network structure and implementation method. The stripline structure is composed of a 3dB coupling bridge and a 90° broadband phase shifter, which has good in-band phase consistency and efficient production and assembly.

[0010] In order to achieve the above-mentioned purpose, the present invention specifically adopts the following technical solutions:

[0011] One aspect of the present invention provides a high consistency sum-difference network structure, including a stripline PCB board assembly, the stripline PCB board assembly includes a broadband sum-difference device part and a power divider component, the sum-difference device part is a stripline structure, the sum-difference device part includes four 3dB coupling bridges and four 90° broadband phase shifters matched with the corresponding 3dB coupling bridges; the four 3dB coupling bridges and the four 90° broadband phase shifters cooperate to superimpose and subtract input signals, and simultaneously output a sum signal, an x-difference signal, a y-difference signal and a double-difference signal, and the double-difference signal is absorbed and matched through a buried resistor and a short-circuit branch;

[0012] The power divider component performs power division or power combination on the sum signal, the x difference signal and the y difference signal, and outputs them to the next level component.

[0013] Specifically, the sum-difference beamforming network has good amplitude and phase consistency.

[0014] In one embodiment, each 3dB coupling bridge adopts a three-branch stripline directional coupler, each of which includes a main channel, a sub-channel, and three coupling branch channels connected between the main channel and the sub-channel, and each of which also includes two signal input ports connected to two ends of the main channel and two signal output ports connected to two ends of the sub-channel;

[0015] Each three-branch stripline directional coupler uses the path difference of microwave signals at different ports after passing through each coupling branch channel, so that the signals at one signal output port of the three-branch stripline directional coupler are superimposed in phase and canceled in opposite phase at another signal output port, thereby forming directional coupling of microwave signals. Figure 2 shown.

[0016] In one embodiment, the summator part includes four signal input ports and four signal output ports, and the power divider component is arranged at the four signal input ports or the four signal output ports. The power divider component realizes power division or power combination of the signal and outputs it to the next level component.

[0017] In one embodiment, the four 3dB coupling bridges are respectively a No. 1 3dB coupling bridge, a No. 2 3dB coupling bridge, a No. 3 3dB coupling bridge, and a No. 4 3dB coupling bridge, and each of the No. 1 3dB coupling bridge, the No. 2 3dB coupling bridge, the No. 3 3dB coupling bridge, and the No. 4 3dB coupling bridge includes two signal input ports and two signal output ports;

[0018] The four 90° broadband phase shifters are respectively a No. 1 90° broadband phase shifter, a No. 2 90° broadband phase shifter, a No. 3 90° broadband phase shifter and a No. 4 90° broadband phase shifter;

[0019] One of the signal input ports of the No. 1 3dB coupling bridge is electrically connected to the No. 1 90° broadband phase shifter, and one of the signal output ports of the No. 1 3dB coupling bridge enters a signal input port of the No. 2 3dB coupling bridge through the No. 2 90° broadband phase shifter; another signal output port of the No. 1 3dB coupling bridge enters a signal input port of the No. 4 3dB coupling bridge through the No. 4 90° broadband phase shifter;

[0020] One of the signal input ports of the No. 3 3dB coupling bridge is electrically connected to the No. 3 90° broadband phase shifter; one of the signal output ports of the No. 3 3dB coupling bridge is electrically connected to another signal input port of the No. 2 3dB coupling bridge; another signal output port of the No. 3 3dB coupling bridge is electrically connected to another signal input port of the No. 4 3dB coupling bridge.

[0021] In one embodiment, each 90° broadband phase shifter includes a main channel and a reference channel, and the main channel is composed of a section of coupled line cascaded to a section of open branch.

[0022] In one embodiment, the input end and the output end of the main channel are respectively connected to a 50-ohm transmission line; and the reference channel is composed of a transmission line with a characteristic impedance of 50 ohms.

[0023] Specifically, the 90° broadband phase shifter is a 90° broadband phase shifter proposed based on the structure of weakly coupled line cascade open-circuit branches. The circuit structure of the 90° broadband phase shifter is as follows: Figure 3 As shown, the main channel consists of a section of coupled line cascaded to an open branch, and the input and output ends are respectively connected to 50 ohm transmission lines; the reference channel is composed of a section of transmission line with a characteristic impedance of 50 ohms.

[0024] In one implementation, the power divider part uses a Wilkinson power divider, and the output port of each Wilkinson power divider is provided with an absorbing buried resistor.

[0025] Specifically, the output port of the Wilkinson power divider is matched by Wilkinson 1-to-2+2 buried resistors + short-circuit branches. If one of the buried resistors fails during long-term use of the product, it will not affect the absorption performance of the overall structure, thereby improving the long-term reliability of this part of the structure.

[0026] In one embodiment, it also includes conductive adhesive films symmetrically arranged on the upper and lower surfaces of the stripline PCB board assembly, metal structural component cavities attached to the outside of each conductive adhesive film, and a pressure plate attached to the outside of each metal structural component cavity.

[0027] Another aspect of the present invention provides a method for realizing a high consistency and poor network structure, which is used to prepare the above-mentioned high consistency and poor network structure, and its assembly method adopts a fully automated pressing method, including the following steps:

[0028] S1. Preparation of components of stripline PCB board assembly: integrating the summing and differential device part, the power divider part, the stripline to coaxial transition section, the SMP connector pad, and the shielding column on the PCB board substrate, the power divider part is connected to the signal output port of the differential device part, the centimeter port of the power divider part is matched to the SMP connector using the stripline to coaxial transition section, and then the SMP connector is through-board soldered using metalized vias + metal pads;

[0029] S2. Attach conductive adhesive films to the upper and lower surfaces of the stripline PCB board assembly, and then attach metal structural component cavities to the outside of each conductive adhesive film. Finally, place a pressing plate on the outside of each metal structural component cavity and press it using high-temperature pressing technology.

[0030] The beneficial effects of the present invention are as follows:

[0031] The invention has a reasonable design, and the broadband sum-difference network has good amplitude and phase consistency in the K band. Compared with the traditional microstrip line + structure cavity manually welded, this form of sum-difference beamforming network has better processing consistency, greatly reduces the difficulty of production and assembly, and improves production efficiency and the yield rate in the assembly process. It can be widely used in engineering batch production tasks. BRIEF DESCRIPTION OF THE DRAWINGS

[0032] In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the following briefly introduces the drawings required for use in the embodiments. It should be understood that the following drawings only show certain embodiments of the present invention and therefore should not be regarded as limiting the scope. For ordinary technicians in this field, other related drawings can be obtained based on these drawings without creative work.

[0033] Figure 1 It is a schematic diagram of the structure of the broadband sum and difference device part.

[0034] Figure 2 It is a structural diagram of a 3dB coupled bridge.

[0035] Figure 3 It is a structural diagram of a 90° broadband phase shifter.

[0036] Figure 4 It is a schematic diagram of the structure of a stripline PCB board assembly.

[0037] Figure 5 It is a network schematic diagram formed by high consistency and poor network structure.

[0038] Figure 6 It is a structural diagram of high consistency and poor network structure. DETAILED DESCRIPTION

[0039] In order to make the technical problems, technical solutions and technical effects of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly and completely described below in conjunction with the drawings in the embodiments of the present invention. Obviously, the described embodiments are part of the embodiments of the present invention, not all of the embodiments. Generally, the components of the embodiments of the present invention described and shown in the drawings here can be arranged and designed in various different configurations.

[0040] Therefore, the following detailed description of the embodiments of the present invention provided in the accompanying drawings is not intended to limit the scope of the invention claimed for protection, but merely represents selected embodiments of the present invention. Based on the embodiments of the present invention, all other embodiments obtained by ordinary technicians in this field without creative work are within the scope of protection of the present invention.

[0041] It should be noted that similar reference numerals and letters represent similar items in the following drawings, so once an item is defined in one drawing, it does not need to be further defined and explained in the subsequent drawings. In addition, the terms "first", "second", etc. are only used to distinguish the description and cannot be understood as indicating or implying relative importance.

[0042] In the description of the embodiments of the present invention, it should be noted that the terms "inside", "outside", "upper", etc. indicate orientations or positional relationships based on the orientations or positional relationships shown in the accompanying drawings, or are the orientations or positional relationships in which the inventive product is usually placed when used. They are only for the convenience of describing the present invention and simplifying the description, and do not indicate or imply that the device or element referred to must have a specific orientation, be constructed and operated in a specific orientation, and therefore cannot be understood as a limitation on the present invention.

[0043] Example 1

[0044] like Figures 1 to 6 As shown, this embodiment provides a high consistency and poor network structure, including a stripline PCB board assembly, and also includes conductive adhesive films symmetrically arranged on the upper and lower surfaces of the stripline PCB board assembly, metal structure cavities attached to the outside of each conductive adhesive film, and a pressure plate attached to the outside of each metal structure cavity;

[0045] The stripline PCB board assembly includes a broadband summator part and a power divider assembly. The summator part is a stripline structure. The summator part includes four 3dB coupling bridges and four 90° broadband phase shifters matched with the corresponding 3dB coupling bridges. The four 3dB coupling bridges and the four 90° broadband phase shifters are matched to superimpose and subtract the input signals, and simultaneously output the sum signal, x difference signal, y difference signal and double difference signal. The double difference signal is absorbed and matched through buried resistance and short-circuit branches.

[0046] The power divider component performs power division or power combination on the sum signal, the x difference signal and the y difference signal, and outputs them to the next level component.

[0047] Specifically, the sum-difference beamforming network has good amplitude and phase consistency.

[0048] Example 2

[0049] This embodiment is further optimized on the basis of embodiment 1, specifically:

[0050] Each 3dB coupling bridge adopts a three-branch stripline directional coupler, each of which includes a main channel, a sub-channel, and three coupling branch channels connected between the main channel and the sub-channel, and each of which also includes two signal input ports connected to both ends of the main channel and two signal output ports connected to both ends of the sub-channel;

[0051] Each three-branch stripline directional coupler uses the path difference of microwave signals at different ports after passing through each coupling branch channel, so that the signals at one signal output port of the three-branch stripline directional coupler are superimposed in phase and canceled in opposite phase at another signal output port, thereby forming directional coupling of microwave signals. Figure 2 shown.

[0052] Example 3

[0053] This embodiment is further optimized on the basis of Embodiment 2, specifically:

[0054] In one embodiment, the summator part includes four signal input ports and four signal output ports, and the power divider component is arranged at the four signal input ports or the four signal output ports. The power divider component realizes power division or power combination of the signal and outputs it to the next level component.

[0055] In one embodiment, the four 3dB coupling bridges are respectively a No. 1 3dB coupling bridge, a No. 2 3dB coupling bridge, a No. 3 3dB coupling bridge, and a No. 4 3dB coupling bridge, and each of the No. 1 3dB coupling bridge, the No. 2 3dB coupling bridge, the No. 3 3dB coupling bridge, and the No. 4 3dB coupling bridge includes two signal input ports and two signal output ports;

[0056] The four 90° broadband phase shifters are respectively a No. 1 90° broadband phase shifter, a No. 2 90° broadband phase shifter, a No. 3 90° broadband phase shifter and a No. 4 90° broadband phase shifter;

[0057] One of the signal input ports of the No. 1 3dB coupling bridge is electrically connected to the No. 1 90° broadband phase shifter, and one of the signal output ports of the No. 1 3dB coupling bridge enters a signal input port of the No. 2 3dB coupling bridge through the No. 2 90° broadband phase shifter; another signal output port of the No. 1 3dB coupling bridge enters a signal input port of the No. 4 3dB coupling bridge through the No. 4 90° broadband phase shifter;

[0058] One of the signal input ports of the No. 3 3dB coupling bridge is electrically connected to the No. 3 90° broadband phase shifter; one of the signal output ports of the No. 3 3dB coupling bridge is electrically connected to another signal input port of the No. 2 3dB coupling bridge; another signal output port of the No. 3 3dB coupling bridge is electrically connected to another signal input port of the No. 4 3dB coupling bridge.

[0059] Specifically, the entire summator part includes four signal input ports and four signal output ports. The four input signals are set to be signal 1, signal 2, signal 3 and signal 4, and the four output signals are set to be signal 5, signal 6, signal 7 and signal 8. The process of signal superposition or subtraction through the entire summator part is as follows:

[0060] Signal 1 enters a signal input port of a No. 1 3dB coupling bridge through a No. 1 90° broadband phase shifter; Signal 2 directly enters another signal input port of a No. 1 3dB coupling bridge; Signal 1 and Signal 2 are superimposed or subtracted in the No. 1 3dB coupling bridge and then output through two signal output ports as Signal 1+Signal 2 and Signal 1-Signal 2 respectively;

[0061] Signal 3 enters a signal input port of the No. 3 3dB coupling bridge through the No. 3 90° broadband phase shifter; Signal 4 directly enters another signal input port of the No. 3 3dB coupling bridge; Signal 3 and Signal 4 are superimposed or subtracted in the No. 3 3dB coupling bridge, and then output through two signal output ports as Signal 3+Signal 4 and Signal 3-Signal 4 respectively;

[0062] Signal 1+Signal 2 enters a signal input port of the No. 2 3dB coupling bridge through the No. 2 90° broadband phase shifter, and Signal 3+Signal 4 directly enters another signal input port of the No. 2 3dB coupling bridge; the two signals of Signal 1+Signal 2 and Signal 3+Signal 4 are superimposed or subtracted in the No. 3 3dB coupling bridge, and then Signal 5 and Signal 6 are output respectively through two signal output ports, and the final signal of Signal 5 is Signal 1+Signal 2 Signal 3+Signal 4, and the final signal of Signal 6 is Signal 1+Signal 2-Signal 3-Signal 4;

[0063] Signal 1-Signal 2 enters one signal input port of the No. 4 3dB coupling bridge through the No. 4 90° broadband phase shifter, and Signal 3-Signal 4 directly enters the other signal input port of the No. 4 3dB coupling bridge; the two signals of Signal 1-Signal 2 and Signal 3-Signal 4 are superimposed or subtracted in the No. 4 3dB coupling bridge and then output as Signal 7 and Signal 8 respectively through two signal output ports. The final signal of Signal 7 is Signal 1-Signal 2+Signal 3-Signal 4, and the final signal of Signal 8 is Signal 1-Signal 2-Signal 3+Signal 4.

[0064] Example 4

[0065] This embodiment is further optimized on the basis of embodiment 3, specifically:

[0066] Each 90° broadband phase shifter includes a main channel and a reference channel. The main channel consists of a section of coupled line cascaded to an open branch. The input and output ends of the main channel are connected to a 50-ohm transmission line respectively; the reference channel is composed of a section of transmission line with a characteristic impedance of 50 ohms.

[0067] Specifically, the 90° broadband phase shifter is a 90° broadband phase shifter proposed based on the structure of weakly coupled line cascade open-circuit branches. The circuit structure of the 90° broadband phase shifter is as follows: Figure 3 As shown, the main channel consists of a section of coupled line cascaded to an open branch, and the input and output ends are respectively connected to 50 ohm transmission lines; the reference channel is composed of a section of transmission line with a characteristic impedance of 50 ohms.

[0068] Example 5

[0069] This embodiment is further optimized based on any one of Embodiments 1 to 4, specifically:

[0070] The power divider part adopts Wilkinson power divider, and the output port of each Wilkinson power divider is provided with an absorbing buried resistor.

[0071] Specifically, the output port of the Wilkinson power divider is matched by Wilkinson 1-to-2+2 buried resistors + short-circuit branches. If one of the buried resistors fails during long-term use of the product, it will not affect the absorption performance of the overall structure, thereby improving the long-term reliability of this part of the structure.

[0072] Example 6

[0073] This embodiment provides a method for realizing a high consistency and poor network structure, which is used to prepare the above-mentioned high consistency and poor network structure, and its assembly method adopts a fully automated pressing method, including the following steps:

[0074] S1. Preparation of components of stripline PCB board assembly: integrating the summing and differential device part, the power divider part, the stripline to coaxial transition section, the SMP connector pad, and the shielding column on the PCB board substrate, the power divider part is connected to the signal output port of the differential device part, the centimeter port of the power divider part is matched to the SMP connector using the stripline to coaxial transition section, and then the SMP connector is through-board soldered using metalized vias + metal pads;

[0075] S2. Attach conductive adhesive films to the upper and lower surfaces of the stripline PCB board assembly, and then attach metal structural component cavities to the outside of each conductive adhesive film. Finally, place a pressing plate on the outside of each metal structural component cavity and press it using high-temperature pressing technology.

[0076] Specifically, 4*6 power division ports (i.e., four Wilkinson power dividers are selected, each Wilkinson power divider includes 6 power division ports, and the four Wilkinson power dividers are distributed in four quadrants, with 6 power division ports in each quadrant) are selected as an example for detailed design analysis. The power divider part uses a Wilkinson power divider. Since the number of power division ports is not 2n, there are two power division ports in each quadrant that use Wilkinson 1-to-2 + 2 buried resistors + short-circuit branches for absorption matching (since the number of power division ports of the Wilkinson power divider is 2n, when 6 power division ports are required, a Wilkinson power divider with 23 power division ports is selected, and 2 power division ports can be absorbed and matched). Figure 4 As shown in 1.

[0077] Each output port of the stripline uses a stripline to coaxial transition section to match the SMP connector, so that the SMP connector is through-board soldered using metalized vias + metal pads. Finally, the 1-to-24 sum-difference beamforming network is processed and assembled using high-temperature pressing technology. The sum-difference beamforming network consists of sum, x-difference, y-difference and 24 sub-ports. The circuit size is 85mm*84mm and the thickness is 1.15mm. The circuit board is fully assembled and pressed with the metal structure cavity and the pressure plate.

Claims

1. A high consistency and poor network structure, characterized in that, The invention comprises a stripline PCB board assembly, wherein the stripline PCB board assembly comprises a broadband summator part and a power divider assembly, wherein the summator part is a stripline structure, and the summator part comprises four 3dB coupling bridges and four 90° broadband phase shifters matched with the corresponding 3dB coupling bridges; the four 3dB coupling bridges and the four 90° broadband phase shifters are matched to superimpose and subtract input signals, and simultaneously output a sum signal, an x-difference signal, a y-difference signal and a double-difference signal, wherein the double-difference signal is absorbed and matched by a buried resistor and a short-circuit branch; The power divider component performs power division or power combination on the sum signal, the x difference signal and the y difference signal, and outputs them to the next level component.

2. A high consistency and poor network structure according to claim 1, characterized in that: Each of the 3dB coupling bridges adopts a three-branch stripline directional coupler, each of the three-branch stripline directional couplers includes a main channel, a secondary channel, and three coupling branch channels connected between the main channel and the secondary channel, and each of the three-branch stripline directional couplers also includes two signal input ports connected to two ends of the main channel and two signal output ports connected to two ends of the secondary channel; Each of the three-branch stripline directional couplers utilizes the path difference of the microwave signal at different ports after passing through each of the coupling branch channels, so that one signal output port of the three-branch stripline directional coupler is superimposed in phase and the other signal output port is canceled in anti-phase, thereby forming directional coupling of the microwave signal.

3. A high consistency and poor network structure according to claim 2, characterized in that: The summator part includes four signal input ports and four signal output ports. The power divider component is arranged at the four signal input ports or the four signal output ports. The power divider component realizes power division or power combination of the signal and outputs it to the next-level component.

4. A high consistency and poor network structure according to claim 3, characterized in that: The four 3dB coupling bridges are respectively a No. 1 3dB coupling bridge, a No. 2 3dB coupling bridge, a No. 3 3dB coupling bridge, and a No. 4 3dB coupling bridge. The No. 1 3dB coupling bridge, the No. 2 3dB coupling bridge, the No. 3 3dB coupling bridge, and the No. 4 3dB coupling bridge each include two signal input ports and two signal output ports. The four 90° broadband phase shifters are respectively a first 90° broadband phase shifter, a second 90° broadband phase shifter, a third 90° broadband phase shifter and a fourth 90° broadband phase shifter; One of the signal input ports of the first 3dB coupling bridge is electrically connected to the first 90° broadband phase shifter, and one of the signal output ports of the first 3dB coupling bridge enters a signal input port of the second 3dB coupling bridge through the second 90° broadband phase shifter; Another signal output port of the first 3dB coupling bridge enters a signal input port of the fourth 3dB coupling bridge through the fourth 90° broadband phase shifter; One of the signal input ports of the No. 3 3dB coupling bridge is electrically connected to the No. 3 90° broadband phase shifter; one of the signal output ports of the No. 3 3dB coupling bridge is electrically connected to another signal input port of the No. 2 3dB coupling bridge; another signal output port of the No. 3 3dB coupling bridge is electrically connected to another signal input port of the No. 4 3dB coupling bridge.

5. A high consistency and poor network structure according to any one of claims 1 to 4, characterized in that: Each of the 90° broadband phase shifters comprises a main channel and a reference channel, wherein the main channel is composed of a section of coupled line cascaded to a section of open branch.

6. A high consistency and poor network structure according to claim 4, characterized in that: The input end and the output end of the main channel are respectively connected to a 50-ohm transmission line; the reference channel is composed of a transmission line with a characteristic impedance of 50 ohms.

7. A high consistency and poor network structure according to claim 1, characterized in that: The power divider part adopts a Wilkinson power divider, and the output port of each Wilkinson power divider is provided with an absorbing buried resistor.

8. A high consistency and poor network structure according to claim 6, characterized in that: It also includes conductive adhesive films symmetrically arranged on the upper and lower surfaces of the stripline PCB board assembly, metal structural component cavities attached to the outside of each of the conductive adhesive films, and a pressure plate attached to the outside of each of the metal structural component cavities.

9. A method for implementing high consistency and poor network structure, characterized in that: Used to prepare a high consistency and poor network structure as described in any one of claims 1 to 8, the assembly method adopts a fully automated pressing method.

10. A method for realizing high consistency and poor network structure according to claim 9, characterized in that: The steps include: S1. Preparation of components of stripline PCB board assembly: integrating the summing and differential device part, the power divider part, the stripline to coaxial transition section, the SMP connector pad, and the shielding column on the PCB board substrate, the power divider part is connected to the signal output port of the differential device part, the centimeter port of the power divider part is matched to the SMP connector using the stripline to coaxial transition section, and then the SMP connector is through-board soldered using metalized vias + metal pads; S2. Attach conductive adhesive films to the upper and lower surfaces of the stripline PCB board assembly, and then attach metal structural component cavities to the outside of each conductive adhesive film. Finally, place a pressing plate on the outside of each metal structural component cavity and perform pressing using high-temperature pressing technology.

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