Communication method based on hybrid beamforming (HBF) network, and related device

Abstract

Embodiments of the present application provide a communication method based on a hybrid beamforming (HBF) network, and a related device. The method comprises: splitting a first total signal to obtain a first optical signal and a second optical signal, wherein the first total signal comprises N optical signals, the N optical signals are signals obtained by using a first modulation scheme, and the first modulation scheme comprises using an electrical signal to drive a laser to change an output light intensity of the laser, or using an external modulator to load an electrical signal onto a light field intensity or a light field amplitude of light outputted by a laser; inputting the first optical signal into a first HBF network to obtain M second sub-signals; performing frequency shifting on the second optical signal, and inputting the second optical signal into the first HBF network to obtain M fourth sub-signals; and combining the M second sub-signals and the M fourth sub-signals in a one-to-one correspondence manner, and outputting the combined signals to M antennas after photoelectric conversion, wherein a phase difference between two adjacent electrical signals among the M electrical signals having undergone photoelectric conversion is a constant.

Description

A communication method and related apparatus based on hybrid beamforming (HBF) networks

[0001] This application claims priority to Chinese Patent Application No. 202411552565.0, filed on October 31, 2024, entitled "A Communication Method and Related Device Based on Hybrid Beamforming (HBF) Network", the entire contents of which are incorporated herein by reference. Technical Field

[0002] This application relates to the field of communication technology, and in particular to a communication method and related apparatus based on a hybrid beamforming (HBF) network. Background Technology

[0003] In wireless communication, beamforming is a signal processing technique that enables directional signal transmission or reception through antenna arrays. Beamforming gives antenna systems spatial selectivity, achieving directional coefficient gain and avoiding spatial interference compared to omnidirectional antennas. Its principle is to weight (i.e., adjust the signal amplitude and phase) the signals transmitted to or from the antenna array elements, causing these signals to undergo constructive interference in some directions and destructive interference in others, thus achieving spatial selectivity. If the weighting process is implemented in the digital domain, it is called digital domain beamforming; if it is implemented in the analog domain, it is called analog domain beamforming; if the weighting process exists in both the digital and analog domains, it is called hybrid beamforming (HBF), as shown in Figure 1. Figure 1 provides a schematic diagram of an HBF antenna system. The input signal Ns is first input to the baseband digital pre-encoder, and then converted into an analog signal by a digital-to-analog converter (DAC). Then, it is input to the RF analog pre-encoder through the radio frequency (RF) chain for beamforming to transmit the antenna signal. Correspondingly, after the receiving end receives the antenna signal, it first synthesizes multiple antenna signals through an RF analog synthesizer, and then connects to an analog-to-digital converter (ADC) through the RF chain to convert the analog signal into a digital signal, which is then input to the baseband digital synthesizer for signal synthesis. The whole process involves the processing of both digital and analog signals.

[0004] Digital domain beamforming has the advantage of carrying multiple data streams, making it crucial for implementing Single User Multiple Input Multiple Output (SU-MIMO) and Multi User Multiple Input Multiple Output (MU-MIMO). However, it requires the number of transceiver units to match the number of antenna array elements. In scenarios with many antenna elements (e.g., high frequencies), this excessive number of transceiver units leads to high system cost and complexity. Analog domain beamforming, on the other hand, allows a single transceiver unit to drive and control multiple antenna array elements based on analog weighting devices. Its disadvantage is that it cannot carry multiple data streams. HBF combines the advantages of both. Based on the characteristics of HBF antenna systems, there are two types of application scenarios: 1) A large number of antenna array elements are required, but a small number of transceiver elements are required. HBF is used to control costs and system complexity. A typical scenario is high frequency. 2) The number of transceiver elements m required is fixed. In order to expand the antenna aperture or scanning range and improve coverage, more than m antenna array elements need to be driven. Therefore, HBF is used. A typical scenario is n transmit antennas and n receive antennas (nTnR).

[0005] Fully connected HBF networks retain the advantage of fewer digital channels compared to traditional HBF networks, while offering significantly better performance than single-connected HBF networks. However, for large-scale antenna systems, such as traditional N×M fully connected HBF networks based on N digital channels and M antenna elements, N×M phase shifters are required. The excessive number of phase shifters leads to high hardware and weighting algorithm complexity. A simplification approach is to implement only the steering vector beam (steering vector weight HBF network) in the N×M fully connected HBF, allowing each beam to control two directions (horizontal and vertical). Theoretically, the minimum number of weights required is 2N. Utilizing the optical domain dispersion effect, introducing an optical domain dispersive phase-shifting network into the steering vector weight HBF network and using microwave photonic signals as input can reduce the number of tuning elements (such as phase shifters) to a minimum of 2N weights without performance loss. However, the dispersion effect of traditional optical domain dispersive phase-shifting networks is too weak, making small-volume integration impossible. Summary of the Invention

[0006] This application discloses a communication method and related device based on a hybrid beamforming (HBF) network, which can achieve small-volume integration.

[0007] In a first aspect, embodiments of this application disclose a communication method based on a hybrid beamforming (HBF) network, comprising:

[0008] The first total signal is split into a first optical signal and a second optical signal. Specifically, the first total signal is obtained by combining N optical signals into a single optical fiber or waveguide. The N optical signals are obtained by photoelectric conversion of N electrical signals through a first modulation method. The first modulation method includes direct modulation or external modulation. Direct modulation is to use an electrical signal to drive the laser to change the output light intensity of the laser. External modulation is to load an electrical signal onto the light field intensity or light field amplitude of the laser output through an external modulator.

[0009] The first optical signal is input into the first HBF network to obtain M second sub-signals. Specifically, the first optical signal first passes through a 1-minute M-channel... h The splitter is divided into M h The first sub-signal of the path, then M h Each of the first sub-signals in the first sub-signal of the path is further processed by a 1-minute interval. v The splitter ultimately produces M second sub-signals, where M = M h *M v ;

[0010] The second optical signal is frequency-shifted and input into the first HBF network to obtain M fourth sub-signals. Specifically, the second optical signal is first frequency-shifted to obtain a third optical signal. The frequency of the frequency-shifted third optical signal is different from the frequency of the first optical signal, that is, the frequency of the signal input into the first HBF network is different. Then, after a 1-minute M-channel... h The splitter is divided into M h The third sub-signal of each path, and then each third sub-signal of each path passes through a 1-minute interval. v The splitter ultimately yields the fourth sub-signal of the M-path;

[0011] The M-channel second sub-signal and the M-channel fourth sub-signal are combined one-to-one and then output to M antennas after photoelectric conversion. Specifically, the M-channel second sub-signal and the M-channel fourth sub-signal are connected to M combiners in sequence to obtain M output signals. The M output signals are then connected to M photodetectors in sequence for photoelectric conversion and output to M antennas. The phase difference between any two adjacent electrical signals in the M electrical signals after photoelectric conversion is a constant, and the frequency of the combined signal is determined by the frequencies of the first optical signal and the third optical signal.

[0012] This method combines optical domain dispersion effect and HBF network to propose a first HBF network, which greatly enhances the dispersion effect compared with the traditional optical domain dispersion phase shifting network. This first HBF network only requires a small length of optical waveguide, so it can be integrated in a small volume.

[0013] In one alternative approach to the first aspect, M hThere is a first transmission distance difference ΔL1 between any two adjacent first sub-signals in the first sub-signal of the path, and M after each first sub-signal is split v There is a second transmission distance difference ΔL2 between any two adjacent second sub-signals in the second sub-signal; M h There is a third transmission distance difference ΔL3 between any two adjacent third sub-signals in the third sub-signal path, and M after each third sub-signal is split. v There is a fourth transmission distance difference ΔL4 between any two adjacent fourth sub-signals.

[0014] In this method, the transmission distances of all first sub-signals, all second sub-signals, all third sub-signals, and all fourth sub-signals are in an arithmetic progression sequence. Because the different light propagation distances lead to different final phases, the phases of the M-channel output signals synthesized by this method after photoelectric conversion are also different; for example, they can be in an arithmetic progression sequence.

[0015] In one alternative approach of the first aspect, the laser is driven by an electrical signal to change the output intensity of the laser, including:

[0016] The bias current or bias voltage of a laser is driven by an electrical signal to change the output light intensity of the laser.

[0017] In this method, the electrical signal is converted into an optical signal using direct modulation, so that the output light intensity of the laser directly carries information without the need for an external modulator, which simplifies the system structure and saves costs.

[0018] In another alternative approach to the first aspect, an electrical signal is applied to the light field intensity or light field amplitude output by the laser via an external modulator, including:

[0019] An electrical signal is applied to the light field intensity output by the laser by using a Mach-Zehnder modulator or an electroabsorption modulator biased at the orthogonal point of light intensity; or, an electrical signal is applied to the light field amplitude output by the laser by using a Mach-Zehnder modulator biased above the zero point of light intensity.

[0020] In this method, an external modulator is used for photoelectric conversion, which allows for flexible adjustment of the position and manner of the information carried by the laser as needed.

[0021] In another alternative method, 1 minute M h The splitter is used to split signals horizontally, 1 to M v A splitter is used to split signals in the vertical direction; or, 1 splitter M h The splitter is used to split signals in the vertical direction, 1 to M vA splitter is used to split signals in the horizontal direction.

[0022] In this method, horizontal and vertical two-dimensional beamforming can be achieved after passing through the first HBF network in either case.

[0023] In one alternative approach, there is a first phase difference between the transmitted signals of adjacent antennas in the horizontal direction among the M antennas, and a second phase difference between the transmitted signals of adjacent antennas in the vertical direction among the M antennas.

[0024] In another alternative approach, when 1 minute M h The splitter is used to split signals horizontally, 1 to M v When a splitter is used to split signals in the vertical direction, the first phase difference is determined based on the wavelength of the first total signal, the first transmission distance difference ΔL1, and the third transmission distance difference ΔL3; the second phase difference is determined based on the wavelength of the first total signal, the second transmission distance difference ΔL2, and the fourth transmission distance difference ΔL4. Similarly, it can be deduced that when 1 M... h The splitter is used to split signals in the vertical direction, 1 to M v When the splitter is used to split signals in the horizontal direction, the first phase difference is determined based on the wavelength of the first total signal, the second transmission distance difference ΔL2 and the fourth transmission distance difference ΔL4, and the third phase difference is determined based on the wavelength of the first total signal, the first transmission distance difference ΔL3 and the third transmission distance difference ΔL3.

[0025] In this method, the direction of the final beamforming can be flexibly adjusted by controlling the wavelength of the input signal.

[0026] In another alternative of the first aspect, the first transmission distance difference ΔL1, the second transmission distance difference ΔL2, the third transmission distance difference ΔL3 and the fourth transmission distance difference ΔL4 are all greater than or equal to zero, but not all of them are zero at the same time.

[0027] By using this method, it can be ensured that the M-channel output signals obtained after photoelectric conversion are different after combining the M-channel second sub-signal and the M-channel fourth sub-signal in a one-to-one correspondence, that is, the phase difference is not zero, so that two-dimensional beamforming can be realized.

[0028] In another alternative approach of the first aspect, the M-path second sub-signals and the M-path fourth sub-signals are combined in a one-to-one correspondence, including:

[0029] M h The j-th sub-signal after splitting the i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v-j+1 path fourth sub-signal combiner, where i is from 1 to M h positive integers, j being 1 to M v A positive integer; where M is a positive integer. h The first sub-signal of the i-th path in the first sub-signal of the (i-1)-th path transmits a first transmission distance difference ΔL1, M more than the first sub-signal of the (i-1)-th path. h The i-th sub-signal of the third path transmits a third transmission distance difference ΔL3 M more than the (i-1)-th sub-signal. v The j-th sub-signal of the second sub-signal transmits a second transmission distance difference ΔL2 M more than the (j-1)-th sub-signal. v The j-th sub-signal of the fourth sub-signal in the M-path carries a fourth transmission distance difference ΔL4 more than the (j-1)-th sub-signal. That is, the transmission distances of the M-path second and M-path fourth sub-signals increase or decrease simultaneously. The phase of the combined signal is the difference between the phases of the two combined signals. Finally, the phase difference between two adjacent electrical signals in the M-path output signal after photoelectric conversion is a constant.

[0030] It can also be understood as M h The j-th sub-signal after splitting the i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v The signal of the fourth sub-signal of path -j+1 is combined with M. h The i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v The phase difference between the signals in the fourth sub-signal of the -j+2 path is a constant.

[0031] The phase of the M-channel output signals synthesized using this method, after photoelectric conversion, is also an arithmetic sequence.

[0032] Secondly, embodiments of this application provide a communication device, which includes a module for performing the method in the first aspect or any possible implementation of the first aspect;

[0033] Alternatively, the communication device includes a processor for performing the method of the first aspect or any possible implementation thereof.

[0034] Thirdly, embodiments of this application provide a communication device, which includes logic circuitry and an interface, the logic circuitry and the interface being coupled; the interface is used for inputting and / or outputting information, wherein:

[0035] A logic circuit is a method for performing the first aspect or any possible implementation of the first aspect.

[0036] Fourthly, embodiments of this application provide a computer-readable storage medium for storing a computer program, wherein:

[0037] When a computer program is executed, it is able to implement the first aspect or any possible implementation of the first aspect. Attached Figure Description

[0038] The accompanying drawings used in the embodiments of this application are described below.

[0039] Figure 1 is a schematic diagram of an HBF antenna system provided in an embodiment of this application;

[0040] Figure 2 is a schematic diagram of the architecture of a communication system provided in an embodiment of this application;

[0041] Figure 3 is a schematic diagram of the architecture of a radar system provided in an embodiment of this application;

[0042] Figure 4 is a schematic diagram of a traditional optical domain dispersion phase-shifting network structure provided in an embodiment of this application;

[0043] Figure 5 is a flowchart illustrating the implementation of a communication method based on an HBF network according to an embodiment of this application;

[0044] Figure 6 is a schematic diagram of a dispersive HBF network structure provided in an embodiment of this application;

[0045] Figure 7 is a flowchart illustrating the implementation of a communication method based on a direct modulation dispersive HBF network according to an embodiment of this application.

[0046] Figure 8 is a schematic diagram of a dispersive HBF network based on direct modulation provided in an embodiment of this application;

[0047] Figure 9 is a schematic diagram of the structure of an externally modulated dispersive HBF network provided in an embodiment of this application;

[0048] Figure 10 is a flowchart illustrating the implementation of a communication method for an externally modulated dispersive HBF network according to an embodiment of this application.

[0049] Figure 11 is a flowchart of another communication method for a dispersive HBF network based on external modulation provided in an embodiment of this application;

[0050] Figure 12 is a schematic diagram of another dispersive HBF network structure provided in an embodiment of this application;

[0051] Figure 13 is a schematic diagram of another dispersive HBF network structure based on direct modulation provided in an embodiment of this application;

[0052] Figure 14 is a schematic diagram of another dispersive HBF network structure based on external modulation provided in an embodiment of this application;

[0053] Figure 15 is a schematic diagram of the structure of a communication device provided in an embodiment of this application;

[0054] Figure 16 is a schematic diagram of the structure of a communication device provided in an embodiment of this application;

[0055] Figure 17 is a schematic diagram of the structure of a communication device provided in an embodiment of this application. Detailed Implementation

[0056] The embodiments of this application are described below with reference to the accompanying drawings.

[0057] In the description of the embodiments of this application, unless otherwise stated, " / " means "or," for example, A / B can mean A or B; the word "and / or" in the text is merely a description of the relationship between related objects, indicating that three relationships can exist. For example, A and / or B can represent: A alone, A and B simultaneously, and B alone. Furthermore, in the description of the embodiments of this application, "multiple" refers to two or more. Hereinafter, the terms "first" and "second" are used for descriptive purposes only and should not be construed as implying or suggesting relative importance or implicitly indicating the number of indicated technical features. Therefore, features defined with "first" and "second" can explicitly or implicitly include one or more of that feature. In the description of the embodiments of this application, unless otherwise stated, "multiple" means two or more.

[0058] The following section introduces the relevant technical concepts involved in the embodiments of this application.

[0059] Microwave Photonics (MWP): Microwave photonics is an important research field worldwide, aiming to achieve the generation, modulation, processing, and reception of microwave signals by studying optical devices and systems that carry microwave signals (frequency from 300MHz to 300GHz). Traditional microwave systems use various electrical devices operating in the microwave frequency band to realize the core functions of microwave signal generation, modulation, signal processing, and reception. However, with the continuous development of applications, people's requirements for the scale and performance of microwave systems are constantly increasing, and the disadvantages of microwave systems composed of purely electrical devices in terms of size, power consumption, insertion loss, bandwidth, frequency band flexibility, electromagnetic interference, process complexity, and manufacturing cost are becoming increasingly prominent. In response to this situation, the field of microwave photonics emerged. Its core idea is to load microwave signals into the optical frequency band, shifting the processing of microwave (electrical) signals to the processing of optical signals. As a result, the vast majority of devices in the system are composed of optical devices, allowing users to enjoy the significant advantages of optical devices, such as ultra-small size, low power consumption, ultra-low insertion loss, ultra-large bandwidth, flexible adjustment of microwave signal frequency bands, resistance to electromagnetic interference, simple manufacturing processes, and low cost. Especially in terms of size, trace loss, and device bandwidth, orders of magnitude improvements can be achieved, reducing costs and improving system compactness. Microwave photonics technology combines photonics and microwave technology, possessing many unique advantages and applications. It can achieve high-speed, high-bandwidth signal processing, utilizing the high-speed propagation characteristics of light to process microwave signals. Optical signals have strong resistance to electromagnetic interference, making them suitable for data transmission in complex environments. Its applications span telecommunications, defense, radar sensing, medical, aerospace, quantum communication, and satellite fields, and its research is still in a period of rapid growth.

[0060] The process of converting microwave (electric) signals into electrical signals is called optical modulation. Direct modulation and external modulation are two common modulation methods for optical modulation.

[0061] Direct modulation: Direct modulation generally refers to converting information into a current signal to modulate the laser driver power supply, thereby directly enabling the output laser to carry information. The intensity or frequency of the light output can be adjusted by directly changing the bias voltage or bias current of the laser. This method does not require an external modulator, has a simple structure, and is low in cost.

[0062] External modulation: External modulation generally refers to loading information onto the laser through an independent modulator, rather than directly changing the laser output of the light source. It changes the characteristics of the optical signal, such as intensity, phase or frequency, through an external modulator (such as an optoelectronic modulator), while the output of the laser remains constant. External modulation has a complex structure, high cost, and requires additional components and driving circuits.

[0063] Intensity modulation: Intensity modulation generally refers to loading information onto the intensity of the laser output by adjusting the current of the laser or an external modulator, thereby giving the laser intensity information.

[0064] Amplitude modulation: Amplitude modulation generally refers to loading information onto the amplitude of a laser, thereby giving the laser amplitude information.

[0065] Optical modulation technology plays an important role in modern communication systems. The choice of which modulation method to use depends on the specific application requirements, cost considerations, and system design complexity.

[0066] This application embodiment is applied to a communication system in which an entity needs to send downlink data and pilot information through an antenna, and another entity needs to receive the indication information through an antenna and be able to send uplink feedback information and transmit data. That is, there is an entity using an antenna to send and receive signals or data. Please refer to Figure 2, which is a schematic diagram of the architecture of a communication system provided in an embodiment of this application. The communication system 20 includes a transmitter 201 and a receiver 202. The receiver 202 and the transmitter 201 can achieve directional signal transmission or reception through an antenna array. For example, the following communication technologies can be used for communication: Long Term Evolution (LTE) system, LTE Frequency Division Duplex (FDD) system, LTE Time Division Duplex (TDD) system, Universal Mobile Telecommunication System (UMTS), Worldwide Interoperability for Microwave Access (WiMAX) system, 5th Generation (5G) mobile communication system, New Radio Access Technology (NR), 6th Generation (6G) mobile communication system, or other radio access technologies. The above communication technologies can be non-standalone (NSA) and / or standalone (SA) modes.

[0067] For example, the transmitter 201 can be a network device, and the receiver 202 can be a terminal. The network device can send downlink data to the terminal via a downlink (DL) through one or more antennas, and the terminal can also send uplink data to the network device via an uplink (UL) through one or more antennas.

[0068] Network equipment refers to access devices that wirelessly connect to the communication system and have wireless transceiver capabilities. This equipment includes, but is not limited to: Base Transceiver Stations (BTS) in Global System for Mobile Communication (GSM) or Code Division Multiple Access (CDMA) networks; NodeBs (NBs) in Wideband Code Division Multiple Access (WCDMA); Evolved Base Stations (NodeBs, eNBs, or e-NodeBs) in Long Term Evolution-Advanced (LTE) or Long Term Evolution-Advanced (LTE-A) systems; Radio Network Controllers (RNCs); Base Station Controllers (BSCs); Base Transceiver Stations (BTSs); Home Base Stations (e.g., home evolved NodeBs or home Node Bs, HNBs); Baseband Units (BBUs); and Next Generation Nodes (NGBs) in 5G NR networks. B, gNB), transmission point (TRP or TP), network nodes or satellites constituting gNB or transmission point, etc. This application does not limit the specific wireless access technology or specific device form used in the network equipment embodiments.

[0069] Terminals can also be user equipment (UE), wireless terminals, mobile terminals, device-to-device (D2D) terminals, vehicle-to-everything (V2X) terminals, machine-to-machine / machine-type communications (M2M / MTC) terminals, Internet of Things (IoT) terminals, light UEs, reduced capability UEs (REDCAP UEs), subscriber units, subscriber stations, mobile stations, remote stations, access points (APs), remote terminals, access terminals, user terminals, user agents, or user devices, etc. For example, it may include mobile phones (or "cellular" phones), smartphones, computers with mobile terminals, portable, pocket-sized, handheld, computer-embedded mobile devices, laptop computers, wireless data cards, tablet computers, wireless modems, etc. Examples include personal communication service (PCS) phones, cordless phones, session initiation protocol (SIP) phones, wireless local loop (WLL) stations, personal digital assistants (PDAs), mobile router devices, and vehicle-mounted terminals (transmission control units), etc. This application does not impose any special restrictions on the specific type of the terminal.

[0070] This application embodiment can also be applied to a phased array radar system. A phased array radar can achieve directional signal transmission and reception through an antenna array, and can have both transmitting and receiving antennas. Please refer to Figure 3, which is a schematic diagram of the architecture of a radar system provided in this application embodiment. The radar system 30 includes a radar 300 and a detection target 303. The radar 300 includes a transmitting unit 301 and a receiving unit 302. The transmitting unit 301 can change the phase of each antenna element to superimpose signals in a specific direction, thereby achieving directional transmission of antenna signals towards the detection target 303. The signal is reflected after contacting the detection target 303. The receiving unit 302 receives the reflected signal for detection and analysis to obtain information. Here, the radar 300 can be a phased array radar, or other radar or equipment that uses multiple antenna arrays to transmit or receive signals. It should be understood that the radar system 30 can include more detection targets and detect multiple targets simultaneously. Detection targets can be airborne or ground targets, possibly including aircraft, ships, etc.

[0071] The steering vector weight (HBF) network has a wide range of applications. It can be applied not only to the system architectures proposed in Figure 2 or Figure 3 above, but also to other scenarios involving multi-antenna transmission or reception. Researching how to reduce the number of weights and tuning elements in the steering vector weight (HBF) network is of great significance to the development and application of the technology.

[0072] To simplify the HBF network, the optical dispersion effect can be utilized. The basic idea is to create a hardware-fixed (purely passive) phase-shifting network, allowing its phase response to change with the wavelength of light. After changing the wavelength of the light source, the phase of all channels in the entire network is refreshed synchronously, thereby decoupling the number of tuning elements and the scale of the HBF network.

[0073] Figure 4 shows a schematic diagram of a traditional optical domain dispersive phase-shifting network structure. The input light is a microwave photonic signal containing two signal components: a carrier component (wavelength λ). c ) and sideband components (frequency λ) s =λ c +Δλ cs , where Δλ cs The microwave photonic signal (which determines the antenna output RF frequency) is input into a passive phase-shifting network, splitting it into multiple paths, each with a different transmission distance or delay. The transmission distance difference between adjacent paths is ΔL. This signal is then converted to the electrical domain and transmitted through the antenna. Therefore, the phase difference between the output RF signals of adjacent antennas... The following relationship must be satisfied:

[0074] in, The phase difference of the signal sideband components. Let be the phase difference of the signal carrier components. It can be seen that due to the carrier sideband wavelength spacing Δλ... cs Too small (e.g., when RF = 28 GHz, Δλ) cs With a wavelength of 0.224 nm, the dispersion effect during in-path transmission is extremely weak, requiring a very large ΔL (e.g., when fiber is used as a delay line, ΔL is on the order of 200 m × M², and when silicon photonics is used as a delay line, ΔL is on the order of 20 cm × M²). This makes small-volume integration impossible, and cost and the scale of the phase-shifting network become bottlenecks. Another problem caused by the weak dispersion effect is that within the tuning range of the light source (e.g., the tuning range of a C-waveguide tunable light source is 30 nm), only one-dimensional dispersion tuning can be covered, making it impossible to achieve horizontal and vertical 2D beamforming.

[0075] Considering the weak dispersion effect of traditional optical domain dispersion phase-shifting networks, another type of phase-shifting network, also based on the optical domain dispersion effect, replaces the unit devices (usually optical fibers or waveguides) in the traditional optical domain dispersion phase-shifting network with resonant or filter devices. This greatly enhances the dispersion effect, thereby reducing the size by orders of magnitude and making it possible to realize large-scale phase-shifting networks on a single chip. However, this technology also has many problems:

[0076] 1) When the resonant / filtering device is modulated, not only does the phase of the output signal change significantly, but the amplitude of the output signal also changes significantly, that is, there is a strong chirp problem. However, the actual steering vector beam weight does not require random amplitude changes when the phase is modulated.

[0077] 2) To achieve phase shifting of microwave photonic signals, the required resonant / filtering devices need extremely high Q values. For example, for microwave frequencies fRF = 1 GHz and fc = 193.1 THz (C-band for optical communication), achieving a -3 dB filter isolation requires a filter Q value of 9.7 × 10⁴. Typically, -3 dB filter isolation is insufficient for practical applications; in real-world applications, the Q value requirements for sub-1 GHz microwave photonic filters are often in the millions. Designing such high-Q microwave photonic filters, precisely controlling the filter center wavelength, and addressing the sensitivity to process errors and environmental temperature changes are all significant engineering challenges.

[0078] Of the two phase-shifting networks mentioned above, the traditional optical domain dispersion phase-shifting network exhibits a weak optical domain dispersion effect, making it impossible to integrate in a small volume and to achieve horizontal and vertical two-dimensional beamforming. While the other phase-shifting network significantly increases the dispersion effect, it also introduces other complex problems that hinder its application. Therefore, this application provides several methods that can address the issues of weak optical domain dispersion, inability to integrate in a small volume, and inability to achieve horizontal and vertical 2D beamforming without introducing other complex problems. The specific methods are as follows.

[0079] Please refer to Figure 5, which is a flowchart illustrating a communication method based on an HBF network according to an embodiment of this application. This method can be implemented based on the transmitter in the architecture shown in Figure 2 or the radar in the architecture shown in Figure 3, or it can be implemented based on other architectures. The method includes, but is not limited to, the following steps:

[0080] Step S501: Split the first total signal to obtain the first optical signal and the second optical signal.

[0081] The first total signal is obtained by combining N optical signals into a single optical fiber or waveguide. Specifically, when the number of digital channels is N, there are a total of N digital electrical signals [s1(t), s2(t), ..., s...]. N (t)] T The N digital electrical signals are converted into N optical signals using a first modulation method. The first modulation method includes direct modulation and external modulation. Direct modulation uses an electrical signal to drive the laser to change its output light intensity. External modulation uses an external modulator to apply an electrical signal to the laser's output light field intensity or amplitude. The vacuum wavelengths of the N optical signals are [λ1, λ2, ..., λ]. N ] T The corresponding frequencies are [w1, w2, ..., w N ] T At this point, the first total signal contains [λ1,λ2,…,λ]. N ] T The optical signals of all wavelengths are divided into a first optical signal and a second optical signal by splitting the first total signal. Therefore, both the first and second optical signals contain [λ1, λ2, ..., λ]. N ] T Optical signals of all wavelengths.

[0082] Step S502: Input the first optical signal into the first HBF network to obtain the M-path second sub-signal.

[0083] The first HBF network combines optical domain dispersion effect and guided vector weight HBF network, and can also be called a dispersive HBF network, as shown in Figure 6. Figure 6 is a schematic diagram of a dispersive HBF network structure provided in an embodiment of this application. It can be seen that the dispersive HBF network includes two symmetrical structures, each of which contains a one-part M. h The splitter (e.g., M1 or M2 in the diagram) and M h One minute M v The two parts share M combiners and M photodetectors. (One M...) h A splitter is used to split a single signal into M... h Road, one minutev A splitter is used to split a single signal into M... v A combiner is used to combine two or more signals into one signal, and a photodetector is used to perform photoelectric conversion to convert optical signals into electrical signals.

[0084] Specifically, after the first optical signal is input into the dispersive HBF network, it first passes through a 1-minute timer. h The splitter (M1) splits the first optical signal into M... h The first sub-signal of the path, M h There is a first transmission distance difference ΔL1 between any two adjacent first sub-signals in the first sub-signal of the path, as shown in Figure 6 M. h The transmission distance (or length of the transmission delay line) of the first sub-signal of the path from top to bottom are [L1 + (M h -1)ΔL1,…,L1+ΔL1,L1] T Then, M h Each of the first sub-signals in the first sub-signal of the path is further processed by a 1-minute interval. v The splitter splits the circuit into M v The second sub-signal of each path, and the M obtained by splitting the first sub-signal of each path. v There is a second transmission distance difference ΔL2 between any two adjacent second sub-signals in the second sub-signal of each path, as shown in Figure 6, where M is obtained by splitting the first sub-signal of each path. v The transmission distance (or length of the transmission delay line) of the second sub-signal of the path, from top to bottom, are [L2 + (M v -1)ΔL2,…,L2+ΔL2,L2] T In the end, a total of M paths are obtained (where M = M h *M v The second sub-signal, where L1 and L2 are the common distances (or the lengths of the common delay lines traversed) between the first and second sub-signals, respectively.

[0085] For example, as shown in Figure 6, let the first sub-signal of the first channel be S1, the first sub-signal of the second channel be S2, and so on, until the Mth sub-signal... h The first sub-signal of the path, Sh, M h The common distance for the transmission of the first sub-signal of the path is L1, which can be understood as M. h The first sub-signal of each path is transmitted through an optical fiber of length L1. The transmission distance of signal S1 is L1, the transmission distance of signal S2 is L1+ΔL1, and so on. Therefore, signal Sh has transmitted L1+(M) times. h -1) The distance of ΔL1; similarly, taking the first sub-signal S1 as an example, it is split into M v After the second sub-signal of the path, M vThe common distance for the transmission of the second sub-signal of each path is L2, and all paths pass through an optical fiber of length L2. The transmission distance of the first path's second sub-signal is L2, the transmission distance of the second path's second sub-signal is L2 + ΔL2, and so on, up to the Mth path. v The transmission distance of the second sub-signal of the path is L2+(M) v -1)ΔL2.

[0086] Step S503: Shift the second optical signal and input it into the first HBF network to obtain the M-path fourth sub-signal.

[0087] Specifically, the second optical signal is first frequency-shifted to obtain the third optical signal. This results in a frequency difference between the third optical signal and the first optical signal. Consequently, the signal frequencies obtained after inputting the same dispersive HBF network will also be different. The role of frequency shifting will be explained in detail in the subsequent combining steps. The amount of frequency shifting, Δw, can be set according to the actual application scenario and application requirements. Δw is not zero.

[0088] Then, the signal is input into the dispersive mixing beamforming (HBF) network. Similar to the first optical signal processing process described above, it first passes through a 1-minute M... h The splitter splits the second optical signal into M... h The third sub-signal of the path, M h There is a third transmission distance difference ΔL3 between any two adjacent third sub-signals in the third sub-signal of the path, as shown in Figure 6. h The transmission distance (or length of the transmission delay line) of the third sub-signal of the path from bottom to top are [L3 + (M h -1)ΔL3,…,L3+ΔL3,L3] T Then, M h Each of the third sub-signals in the path is further processed by a 1-minute interval. v The splitter splits the circuit into M v The fourth sub-signal of each path, and M obtained by branching the third sub-signal of each path. v There is a fourth transmission distance difference ΔL4 between any two adjacent fourth sub-signals in the fourth sub-signal of each path, as shown in Figure 6, where M is obtained by splitting the third sub-signal of each path. v The transmission distance (or length of the transmission delay line) of the fourth sub-signal of the path, from bottom to top, are [L4 + (M v -1)ΔL4,…,L4+ΔL4,L4] T In the end, a total of M paths are obtained (where M = M h *M vThe fourth sub-signal, where L3 and L4 are the common distances (or the lengths of the common delay lines traversed) of the third and fourth sub-signals, respectively. Referring to the description of the transmission distances of the first and second sub-signals in step S502, similarly, M can be obtained. h The third sub-signal of each path and the M obtained by splitting the third sub-signal of each path v The transmission distance of the fourth sub-signal is shown in Figure 6.

[0089] It is worth noting that the first transmission distance difference ΔL1, the second transmission distance difference ΔL2, the third transmission distance difference ΔL3, and the fourth transmission distance difference ΔL4 are all greater than or equal to zero, but not all of them are zero at the same time. Their specific values ​​can be set according to the actual needs of the scenario.

[0090] Step S504: Combine the M-channel second sub-signal with the M-channel fourth sub-signal one by one, and output them to the M antennas after photoelectric conversion.

[0091] Specifically, the M second and M fourth sub-signals are sequentially connected to M combiners to obtain M output signals. These M output signals are then sequentially connected to M photodetectors for photoelectric conversion before being output to M antennas. The phase difference between any two adjacent signals in the resulting electrical signals is a constant. The signals emitted by the M antennas ultimately form a fixed-direction two-dimensional beam. By controlling the phase difference of the emitted signals from the M antennas, the shape and direction of the beamform can be controlled.

[0092] The frequencies of the M antenna-transmitted signals obtained after combining depend on the frequencies of the first and third optical signals. For example, the frequencies of the M antenna-transmitted signals are equal to the sum of the frequencies of the first and third optical signals. Once the target frequency of the desired antenna-transmitted signal is determined, the frequency of the first total signal can be determined by controlling the amount of frequency shift. Generally, antennas transmit high-frequency signals, but the signal frequency input to the dispersive HBF network is relatively low. In this case, frequency shifting can be used to control the amount of frequency shift to achieve the target high-frequency antenna-transmitted signal after combining.

[0093] Specifically, the merging method can be to combine M... h The j-th word signal after the first sub-signal of the i-th sub-signal in the first sub-signal of ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v -j+1 channels are combined to obtain M output signals. These M output signals are then sequentially connected to M photoelectric converters for photoelectric conversion, and the results are output to M antennas, where i ranges from 1 to M. h positive integers, j being 1 to M v positive integers, where Mh The first sub-signal of the i-th path in the first sub-signal of the (i-1)-th path transmits a first transmission distance difference ΔL1, M more than the first sub-signal of the (i-1)-th path. h The i-th sub-signal of the third path transmits a third transmission distance difference ΔL3 M more than the (i-1)-th sub-signal. v The j-th sub-signal of the second sub-signal transmits a second transmission distance difference ΔL2 M more than the (j-1)-th sub-signal. v The j-th sub-signal of the fourth sub-signal in the M-way transmits a fourth transmission distance difference ΔL4 more than the (j-1)-th sub-signal of the fourth sub-signal. That is, the transmission distances of the M-way second sub-signals and the M-way fourth sub-signals increase or decrease simultaneously. The phase of the output signal after combining is the difference between the phases of the two combined signals. Finally, the phase difference between two adjacent output signals in the M-way output signal after combining is a constant.

[0094] The combination path can also be understood as M. h The j-th sub-signal after splitting the i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v The signal of the fourth sub-signal of path -j+1 is combined with M. h The i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v The phase difference between the signals in the fourth sub-signal combiner of the -j+2 path is a constant, where M h The first sub-signal of the i-th path in the first sub-signal of the (i-1)-th path transmits a first transmission distance difference ΔL1, M more than the first sub-signal of the (i-1)-th path. h The i-th sub-signal of the third path transmits a third transmission distance difference ΔL3 M more than the (i-1)-th sub-signal. v The j-th sub-signal of the second sub-signal transmits a second transmission distance difference ΔL2 M more than the (j-1)-th sub-signal. v The j-th sub-signal of the fourth sub-signal in the path has a transmission distance difference ΔL4 that is greater than that of the (j-1)-th sub-signal.

[0095] There are many specific scenarios for route merging; three examples are given below:

[0096] In scenario one, the first transmission distance difference ΔL1, the second transmission distance difference ΔL2, the third transmission distance difference ΔL3, and the fourth transmission distance difference ΔL4 are all greater than zero. During optical signal transmission, if two optical signals (e.g., optical signals transmitted from different paths) travel different distances, the phase of the light waves at each position will change with the propagation distance. Therefore, their phases at a given point will also be different. That is, there is a fixed phase difference between any two adjacent second sub-signals in the M-path second sub-signals, and there is also a fixed phase difference between any two adjacent fourth sub-signals in the M-path fourth sub-signals. In this case, the combining can be understood as M... h The M signal after splitting the first sub-signal of the path with the longest transmission distance in the first sub-signal of the path. v The second sub-signal of the path with the longest transmission distance and M h M, the third sub-signal with the shortest transmission distance in the path, after being split. v The fourth sub-signal of the path with the shortest transmission distance is connected to the same combiner for combining; this process is repeated until M. h M, the first sub-signal of the path with the shortest transmission distance, after being split. v The second sub-signal of the path with the shortest transmission distance and M h The M signal after splitting the third sub-signal of the path with the longest transmission distance. v The fourth sub-signal with the longest transmission distance in each path is connected to the same combiner for combining. The phase of the output signal after combining the two signals is obtained by subtracting the phases of the two signals. Therefore, in this case, the phase value of the final combined output signal covers a wider range.

[0097] For example, suppose the phases of the second sub-signals of the M paths are respectively The phases of the fourth sub-signal of the M-path are respectively At this time, the phase values ​​of the M output signals after combining are respectively The phase value coverage range is:

[0098] Scenario 2: The first transmission distance difference ΔL1 and the second transmission distance difference ΔL2 are both zero, and at least one of the third transmission distance difference ΔL3 and the fourth transmission distance difference ΔL4 is not zero. This means that the transmission distances of the M-path second sub-signals are the same and there is no phase difference, while there is a fixed phase difference between adjacent fourth sub-signals in the M-path. In this case, the combining can be understood as M... h The M-path second sub-signal obtained by splitting the first sub-signal of the path M is then sequentially coupled with M h The M-channel fourth sub-signal obtained by splitting the third sub-signal of the first channel is connected to the same combiner for combination. In this case, the phase value coverage of the final combined output signal is smaller than that in the first case.

[0099] For example, suppose the phases of the second sub-signals of the M paths are respectively The phases of the fourth sub-signal of the M-path are respectively At this time, the phase values ​​of the M output signals after combining are respectively Then the phase value coverage range is:

[0100] In scenario three, at least one of the first transmission distance difference ΔL1 and the second transmission distance difference ΔL2 is not zero, and both the third transmission distance difference ΔL3 and the fourth transmission distance difference ΔL4 are zero. This means that there is a fixed phase difference between adjacent second sub-signals in the M-path second sub-signals, and the M-path fourth sub-signals have the same transmission distance and no phase difference. In this case, the combining situation is similar to scenario two, and the phase value coverage of the final combined output signal is relatively small.

[0101] For example, suppose the phases of the second sub-signals of the M paths are respectively The phases of the fourth sub-signal of the M-path are respectively At this time, the phase values ​​of the combined M-channel output signals are respectively Then the phase value coverage range is:

[0102] In the method shown in Figure 5, the dispersive HBF network can be either the network structure shown in Figure 6 or the network structure shown in Figure 12. Comparing Figures 6 and 12, it can be found that the overall structure of the dispersive HBF network shown in Figure 12 is similar to that of the HBF network shown in Figure 6, both being symmetrical structures, and each side contains a 1-part M. h The splitter and M h One minute M v The system consists of a splitter, M combiners, and M photodetectors. Similarly, after the first optical signal is input into the dispersive HBF network, it passes through a 1-splitter M-splitter. h The splitter splits the first optical signal into M... h The first sub-signal of the path, M h Each of the first sub-signals in the first sub-signal of the path is further processed by a 1-minute interval. v The splitter splits the circuit into M vThe second sub-signal is used to obtain M second sub-signals; similarly, the second optical signal is frequency-shifted and input into the dispersive HBF network to obtain M fourth sub-signals. The difference is that in the dispersive HBF network in Figure 12, the transmission distances between all first sub-signals are not equal, the transmission distances between all second sub-signals are not equal, the transmission distances between all third sub-signals are not equal, and the transmission distances between all fourth sub-signals are not equal. However, the phase of the electrical signal after combining and photoelectrically converting the M second and M fourth sub-signals is an arithmetic progression sequence. That is, the phase difference between any two adjacent electrical signals in the M electrical signals obtained after combining and photoelectrically converting the M second and M fourth sub-signals is a constant. It can also be understood that the M transmission distance differences obtained by subtracting the transmission distances of the M second and M fourth sub-signals are an arithmetic progression sequence, namely [L0, L0+ΔL0, L0+2ΔL0, ..., L0+(M-1)ΔL0].

[0103] It is worth noting that the above 1 minute M h The splitter and 1M v There are several possible branching configurations for a splitter; two examples are given below:

[0104] Possibly one, 1 minute M h The splitter splits the circuit horizontally, 1 splitter M v The splitter splits the signal along the vertical direction. At this time, the phase difference between the signals of adjacent antennas in the vertical direction in the combined M antennas is a constant, which depends on the wavelength of the first total signal, the second transmission distance difference ΔL2 and the fourth transmission distance difference ΔL4. The phase difference between the signals of adjacent antennas in the horizontal direction in the combined M antennas is also a constant, which depends on the wavelength of the first total signal, the first transmission distance difference ΔL1 and the third transmission distance difference ΔL3.

[0105] Possible two, 1 minute M h The splitter splits the circuit vertically, 1 splitter M v The splitter splits the signal along the horizontal direction. At this time, the phase difference between the horizontally adjacent antennas in the M-channel antennas after combining is a constant, which depends on the wavelength of the first total signal, the first transmission distance difference ΔL2, and the third transmission distance difference ΔL4. The phase difference between the vertically adjacent antennas in the M-channel antennas after combining is also a constant, which depends on the wavelength of the first total signal, the second transmission distance difference ΔL1, and the fourth transmission distance difference ΔL3.

[0106] In the method shown in Figure 5, the beam pointing can be flexibly adjusted by regulating the signal wavelength, reducing the number of weights and tuning elements, and because of the 1-segment M in the dispersive HBF network... hThe splitter and 1M v The splitter can split the signal in the horizontal and vertical directions respectively, so the signal output by the dispersive HBF network can achieve two-dimensional horizontal and vertical beamforming.

[0107] The specific implementation of the communication method based on HBF network shown in Figure 5 may vary depending on the scenario. For ease of understanding, the following explanations will cover several cases.

[0108] Please refer to Figure 7, which is a flowchart of a communication method based on a direct modulation dispersive HBF network provided in an embodiment of this application. That is, the output of the laser is directly changed by an electrical signal to perform photoelectric conversion. This method can be implemented based on the transmitter in the architecture shown in Figure 2 or the radar in the architecture shown in Figure 3, or it can be implemented based on other system architectures. The method includes, but is not limited to, the following steps:

[0109] Step S701: Directly drive the polarization current or polarization voltage of the laser using an electrical signal.

[0110] Specifically, as shown in Figure 8, which provides a schematic diagram of a dispersive HBF network based on direct modulation, when the number of digital channels of the input signal on the left is N, there are a total of N digital electrical signals [s1(t), s2(t), ..., s N (t)] T Using N digital electrical signals to drive the bias current or bias voltage of N lasers respectively, the output light intensity of the N lasers is directly changed by controlling the bias current or bias voltage, thus enabling the output light intensity of the N lasers to carry information, realizing the conversion of N digital electrical signals into N optical signals. The vacuum wavelengths of the resulting N optical signals are [λ1, λ2, ..., λ]. N ] T The corresponding frequencies are [w1, w2, ..., w N ] T Where the superscript T denotes transpose. Taking the first digital signal as an example, the output optical field of the first digital electrical signal s1(t) obtained in this way can be expressed as: Where c1 represents the optical carrier.

[0111] Step S702: Split the first total signal to obtain the first optical signal and the second optical signal.

[0112] Specifically, the first total signal is obtained by combining the N optical signals obtained after photoelectric conversion into a single optical fiber or waveguide. In this case, the first total signal contains [λ1, λ2, ..., λ]. N ] TThe optical signals contain all wavelengths, therefore the first and second optical signals obtained after splitting are completely identical, both containing [λ1, λ2, ..., λ]. N ] T Optical signals of all wavelengths.

[0113] Step S703: Input the first optical signal into the first HBF network to obtain the M-path second sub-signal.

[0114] The specific implementation method and related information for this step can be found in step S502 above, and will not be repeated here.

[0115] Step S704: Shift the second optical signal and input it into the first HBF network to obtain the M-path fourth sub-signal.

[0116] The specific implementation method and related information for this step can be found in step S503 above, and will not be repeated here.

[0117] Step S705: Combine the M-channel second sub-signal with the M-channel fourth sub-signal one by one, and output them to the M antennas after photoelectric conversion.

[0118] For details on the specific implementation method and possible situations of this step, please refer to step S504 above, which will not be repeated here.

[0119] Although the description of the dispersive HBF network in this embodiment is the same as that in the method embodiment shown in Figure 5, the input signal to the dispersive HBF network will differ depending on the situation, such as the difference in the first modulation method. The following provides a detailed explanation of specific cases in this method embodiment. Taking the first digital signal as an example, the output light field obtained by the first digital electrical signal s1(t) driving the first laser can be expressed as... Where c1 represents the optical carrier, input to the dispersive HBF network, and finally combined to obtain the output transmitted signals of M antennas. If we ignore the second-order term of the square-law detection of the photodetector and only focus on the cross-term signal, the M corresponding to the first row in Figure 8 are shown. v Taking one antenna as an example, the M after combining v Each signal can be represented as:

[0120] Where, n e ΔL0, L1, L2, and L3 are the common distances for signal transmission (common lengths of delay lines), and ΔL1, ΔL2, ΔL3, and ΔL4 are the corresponding transmission distance differences (differences in delay line lengths). These values ​​can be set according to the actual application scenario and application requirements.

[0121] The above formula represents M after photoelectric conversion. vThe coherence term of the signal is the product of the optical fields of the two combined signals, frequency-converted to frequency Δw, and carries an optical phase related to the delay line length. Since the difference between the optical fields of the two combined signals lies only in the existence of a delay, which is relatively small compared to the rate of signal change, the optical fields of the two combined signals are very close. Therefore, the above equation can be approximated as:

[0122] It can be seen that M v The phases on each antenna are as follows:

[0123] The phase difference between adjacent antennas in the vertical dimension is:

[0124] It can be observed that the phase difference between adjacent antennas in the vertical dimension is a constant, and its magnitude depends on the wavelength λ1 and the magnitudes of the second transmission distance ΔL2 and the fourth transmission distance ΔL4.

[0125] Similarly, it can be deduced that the phase difference between adjacent antennas in the horizontal dimension is It is also a constant, and its magnitude depends on the wavelength λ1 and the magnitudes of the first transmission distance ΔL1 and the third transmission distance ΔL3. When the first transmission distance ΔL1, the second transmission distance ΔL2, the third transmission distance ΔL3, and the fourth transmission distance ΔL4 are determined, it mainly depends on the wavelength λ1. The beam pointing can be flexibly adjusted by changing the wavelength λ1. Therefore, after the first digital electrical signal s1(t) passes through the directly modulated dispersive HBF network, it can form a fixed-pointing two-dimensional beam in the spatial domain, and its beam pointing depends on the magnitude of its wavelength λ1.

[0126] Using the method in the embodiments of this application, each wavelength corresponds to a beam direction, and the N digital electrical signals can control the antenna direction by changing the wavelength of the input signal, thereby realizing an N-drive-M (N electrical signals drive M antenna arrays) dispersive HBF network.

[0127] Similarly, in the method shown in Figure 7, direct modulation can be combined with the network structure shown in Figure 6 (as shown in Figure 8), or direct modulation can be combined with the HBF network structure shown in Figure 12 (as shown in Figure 13). Compared with the structure shown in Figure 8, although the transmission distances of the first, second, third, and fourth sub-signals in the dispersive HBF network shown in Figure 13 are different from those shown in Figure 8, the phase difference between adjacent signals in the final signal after the second and fourth sub-signals are combined one-to-one and converted by photoelectric conversion is a constant, that is, the final effect is the same as that of the network structure shown in Figure 8.

[0128] Please refer to Figure 9, which is a schematic diagram of the structure of an externally modulated dispersive HBF network provided in an embodiment of this application. Figure 10 is a flowchart of a communication method for an externally modulated dispersive HBF network provided in an embodiment of this application. This method can be implemented based on the transmitter in the architecture shown in Figure 2 or the radar in the architecture shown in Figure 3, or it can be implemented based on other architectures. The method includes, but is not limited to, the following steps:

[0129] Step S1001: Apply the electrical signal to the optical field intensity through an external modulator.

[0130] Specifically, N digital electrical signals are applied to the optical field intensity of N lasers through devices such as Mach-Zehnder modulators or electro-absorption modulators at the orthogonal points of optical intensity. This allows the output light intensity of the N lasers to carry information, thereby realizing the conversion from N digital electrical signals to N optical signals. When the number of digital channels is N, there are a total of N digital electrical signals [s1(t), s2(t), ..., s...]. N (t)] T The vacuum wavelengths of the obtained N optical signals are [λ1,λ2,…,λ]. N ] T The corresponding frequencies are [w1, w2, ..., w N ] T Where the superscript T denotes transpose. Taking the first digital signal as an example, the output optical field of the first digital electrical signal s1(t) obtained in this way can be expressed as: The output light field obtained is the same as that obtained by the direct modulation method shown in Figure 4. In this case, the modulator in Figure 9 can be a Mach-Zehnder modulator or an electroabsorption modulator, etc.

[0131] Step S1002: Split the first total signal to obtain the first optical signal and the second optical signal.

[0132] For a detailed description, please refer to step S702, which will not be repeated here.

[0133] It is worth noting that the first and second optical signals obtained are the same as those in Figure 7. They are then input into the dispersive HBF network, which is the same as the dispersive HBF network in Figure 5.

[0134] Step S1003: Input the first optical signal into the first HBF network to obtain the M-path second sub-signal.

[0135] For a detailed description, please refer to step S502, which will not be repeated here.

[0136] Step S1004: Shift the second optical signal and input it into the first HBF network to obtain the M-path fourth sub-signal.

[0137] For a detailed description, please refer to step S503, which will not be repeated here.

[0138] Step S1005: Combine the M-channel second sub-signal and the M-channel fourth sub-signal one by one, and output them to the M antennas after photoelectric conversion.

[0139] For a detailed description, please refer to step S504, which will not be repeated here.

[0140] It is worth noting that the optical field of the optical signal obtained by photoelectric conversion through the external modulation method in step S1001 is the same as the optical field of the optical signal obtained by photoelectric conversion through the direct modulation method in step S701 of the embodiment provided in Figure 7 or Figure 8. That is, the input signal to the dispersive HBF network is the same. Therefore, the signal obtained after dispersive HBF and the beamforming effect are the same as those provided by the embodiment shown in Figure 7 or Figure 8, and the final effect is also the same. The specific formula will not be explained here.

[0141] Please refer to Figure 11. Figure 11 is a flowchart of another communication method based on an externally modulated dispersive HBF network provided in this application embodiment. This method can be implemented based on the transmitter in the architecture shown in Figure 2 or the radar in the architecture shown in Figure 3, or it can be implemented based on other architectures. The method includes, but is not limited to, the following steps:

[0142] Step S1101: Apply the electrical signal to the optical field amplitude through an external modulator.

[0143] Specifically, N digital electrical signals are applied to the optical field amplitudes of N lasers via devices such as Mach-Zehnder modulators above zero intensity, so that the optical field amplitudes of the N laser outputs carry information, thereby realizing the conversion from N digital electrical signals to N optical signals. When the number of digital channels is N, there are a total of N digital electrical signals [s1(t), s2(t), ..., s...]. N (t)] T The vacuum wavelengths of the obtained N optical signals are [λ1,λ2,…,λ]. N ] T The corresponding frequencies are [w1, w2, ..., w N ] T Where the superscript T denotes transpose. Taking the first digital signal as an example, the output optical field of the first digital electrical signal s1(t) obtained in this way can be expressed as: Where c1 represents the optical carrier. A schematic diagram of the dispersive HBF network based on external modulation in this embodiment can be found in Figure 9, where the external modulator is a Mach-Zehnder modulator, etc.

[0144] Step S1102: Split the first total signal to obtain the first optical signal and the second optical signal.

[0145] The first total signal is obtained by combining N optical signals into a single optical fiber or waveguide. In this case, the first total signal contains [λ1, λ2, ..., λ]. N ] T The optical signals contain all wavelengths, therefore the first and second optical signals after splitting are completely identical, both containing [λ1, λ2, ..., λ]. N ] T Optical signals of all wavelengths.

[0146] It is worth noting that after obtaining the first and second optical signals, they are input into the dispersive HBF network, which is the same as the dispersive HBF network in Figure 5 or Figure 6.

[0147] Step S1103: Input the first optical signal into the first HBF network to obtain the M-path second sub-signal.

[0148] For a detailed description, please refer to step S502, which will not be repeated here.

[0149] Step S1104: Shift the second optical signal and input it into the first HBF network to obtain the M-path fourth sub-signal.

[0150] For a detailed description, please refer to step S503, which will not be repeated here.

[0151] Step S1105: Combine the M-channel second sub-signal with the M-channel fourth sub-signal one by one, and output them to the M antennas after photoelectric conversion.

[0152] For a detailed description, please refer to step S504. The merging here is also divided into three cases. For a detailed description, please refer to the corresponding description of the embodiment method provided in Figure 5 or Figure 6 above. They will not be repeated here.

[0153] It is worth noting that, since the modulation method in step S1101 in this embodiment is different from that in step S701, the resulting representation of the first total signal light field is different from that obtained in step S701. Therefore, the output signal after combining after inputting the same dispersive HBF network is also different.

[0154] At this point, the combined signal, taking the first digital signal as an example, the output light field obtained by the first digital electrical signal s1(t) driving the first laser can be expressed as: Where c1 represents the optical carrier, after passing through the same dispersive HBF network as in the above embodiment, the signals transmitted by the M antennas are obtained. Ignoring the second-order term of the square-law detection of the photodetector, only the cross-term signal is considered, which corresponds to the M signals after the first row of combining shown in Figure 10. v Taking one antenna signal as an example, M v The individual antenna signals can be represented as follows:

[0155] Where, n e ΔL0, L1, L2, and L3 are the common distances for signal transmission (common lengths of delay lines), and ΔL1, ΔL2, ΔL3, and ΔL4 are the corresponding transmission distance differences (differences in delay line lengths). These values ​​can be set according to the actual application scenario and application requirements.

[0156] The product of the carrier and the signal can be extracted from the frequency domain, yielding:

[0157] The above formula can be approximated as:

[0158] It can be seen that M v The phases on each antenna are as follows:

[0159] The phase difference between adjacent antennas in the vertical dimension is:

[0160] It can be observed that the phase difference between adjacent antennas in the vertical dimension is a constant, and its magnitude depends on the wavelength λ1 and the magnitudes of the second transmission distance ΔL2 and the fourth transmission distance ΔL4. Similarly, the phase difference between adjacent antennas in the horizontal dimension is... It is also a constant, and its magnitude depends on the wavelength λ1 and the magnitudes of the first transmission distance ΔL1 and the third transmission distance ΔL3.

[0161] As can be seen, the phases of the M antennas obtained by the method provided in the embodiment shown in Figure 11 are exactly the same as the phases of the M antennas obtained in the method embodiment provided in Figure 7 or Figure 8. Therefore, the effect after passing through the dispersive HBF network is also exactly the same, and a fixed-pointing two-dimensional beam can be formed in the spatial domain. The beam direction depends on the wavelength λ1.

[0162] Using the method in the embodiments of this application, each wavelength corresponds to a beam direction, and the N digital electrical signals can control the antenna direction by changing the wavelength of the input signal, thereby realizing an N-drive-M (N electrical signals drive M antenna arrays) dispersive HBF network.

[0163] It is understood that the input signal of the dispersive HBF network based on direct modulation shown in Figure 13 is the same as that of the dispersive HBF network based on direct modulation shown in Figure 8, and the final result is also the same. Therefore, the final effect of the dispersive HBF network based on direct modulation shown in Figure 13 can be directly referred to the description of the embodiment shown in Figure 8. An N-driven M dispersive HBF network can not only perform two-dimensional beamforming in both horizontal and vertical directions, but also flexibly adjust the beam direction by changing the signal wavelength. The specific details can be referred to the corresponding descriptions in Figure 5, Figure 7, or Figure 8, which will not be repeated here.

[0164] Similarly, in the communication method of the dispersive HBF network based on external modulation shown in Figure 10 or Figure 11, external modulation can be combined with the network structure shown in Figure 6 (as shown in Figure 9), or it can be combined with the HBF network structure shown in Figure 12 (as shown in Figure 14). Compared with the structure shown in Figure 9, although the transmission distances of the first, second, third, and fourth sub-signals in the dispersive HBF network shown in Figure 14 are different from those shown in Figure 9, the phase difference between adjacent signals in the final signal after the second and fourth sub-signals are combined one-to-one and converted by photoelectric conversion is a constant. That is, the final effect is the same as that of the network structure shown in Figure 9. Therefore, the effect of the other dispersive HBF network based on external modulation shown in Figure 14 can be referred to the description of the method in Figure 10 or Figure 11.

[0165] The following describes the communication device provided in the embodiments of this application.

[0166] This application divides the communication device into functional modules according to the above method embodiments. For example, each function can be divided into its own functional modules, or two or more functions can be integrated into one processing module. The integrated modules can be implemented in hardware or as software functional modules. It should be noted that the module division in this application is illustrative and only represents one logical functional division; other division methods may be used in actual implementation. The communication device of the embodiments of this application will be described in detail below with reference to Figures 15 to 17.

[0167] Figure 15 is a schematic diagram of a communication device provided in an embodiment of this application. As shown in Figure 15, the communication device includes a processing module 1501, a transceiver module 1502, and a modulation module 1503. The transceiver module 1502 can implement corresponding communication functions, the processing module 1501 is used for data or signal processing, such as performing the function of a dispersive HBF network, and the modulation module can process signals, such as performing a first modulation function. The transceiver module 1502 can also be called an interface, a communication interface, or a communication module, etc., and the transceiver module can also be a radio frequency module or an antenna.

[0168] In some embodiments of this application, the communication device can be used to perform the actions performed by the transmitting end (e.g., network equipment such as satellites) or radar in the above method embodiments. For example, the communication device can be the network equipment itself or a chip or functional module (e.g., an antenna system) configurable within the network equipment. Specifically, the transceiver module 1502 is used to perform transmission and reception related operations in the above method embodiments, and the processing module 1501 is used to perform processing related operations in the above method embodiments. The processing module 1501 can perform corresponding operations by calling a computer program or by performing corresponding operations through corresponding hardware circuits (e.g., based on devices such as combiners and splitters). The transceiver module 1502 can perform transmission and reception operations independently or under the control of the processing module 1501.

[0169] For example, the communication device shown in Figure 15 can be a network device or a component within a network device (such as an antenna system, chip, etc.). The processing module 1501 and the transceiver module 1502 in this communication device can respectively perform the following operations:

[0170] The processing module 1501 splits the first total signal into a first optical signal and a second optical signal through a splitter. The first total signal includes N optical signals, which are signals obtained by using a first modulation method. The first modulation method includes using an electrical signal to drive the laser to change the output light intensity of the laser or using an external modulator to load an electrical signal onto the light field intensity or light field amplitude of the laser output.

[0171] Processing module 1501 inputs the first optical signal into the first HBF network to obtain M second sub-signals, wherein the M second sub-signals are generated by processing the first optical signal through a 1-minute M-channel processing module. h The splitter is divided into M h After the first sub-signal of the road, it passes through M respectively. h 1 minute each v The result is obtained from the splitter, M = M h *M v ;

[0172] Processing module 1501 shifts the second optical signal and inputs it into the first HBF network to obtain M fourth sub-signals, wherein the M fourth sub-signals are obtained by shifting the second optical signal and processing it for 1 minute. h The splitter is divided into M h After the third sub-signal of the road, it passes through M respectively. h 1 minute each v The result is obtained from the splitter;

[0173] The processing module 1501 combines the M second sub-signals and the M fourth sub-signals one-to-one through a combiner, and after photoelectric conversion, outputs them to the M antennas through the transceiver module 1502. The phase difference between two adjacent electrical signals in the M electrical signals after photoelectric conversion is a constant.

[0174] In one alternative implementation:

[0175] M h There is a first transmission distance difference ΔL1 between any two adjacent first sub-signals in the first sub-signal of the path, and M after each first sub-signal is split v There is a second transmission distance difference ΔL2 between any two adjacent second sub-signals in the second sub-signal;

[0176] M h There is a third transmission distance difference ΔL3 between any two adjacent third sub-signals in the third sub-signal path, and M after each third sub-signal is split. v There is a fourth transmission distance difference ΔL4 between any two adjacent fourth sub-signals.

[0177] In one alternative implementation, regarding the use of electrical signals to drive the laser to change the output light intensity, the processing module 1501 is specifically used for:

[0178] The bias current or bias voltage of a laser is driven by an electrical signal to change the output light intensity of the laser.

[0179] In one alternative implementation, an electrical signal is applied to the light field intensity or amplitude output by the laser via an external modulator. Specifically, the processing module 1501 is used for:

[0180] An electrical signal is applied to the light field intensity output by the laser by using a Mach-Zehnder modulator or an electroabsorption modulator biased at the orthogonal point of light intensity.

[0181] Alternatively, an electrical signal can be applied to the amplitude of the laser output light field by using a Mach-Zehnder modulator biased above the zero point of light intensity.

[0182] In one alternative implementation, 1 minute M h The splitter is used to split signals horizontally, 1 to M v The splitter is used to split signals in the vertical direction, or, 1 to M. h The splitter is used to split signals in the vertical direction, 1 to M v A splitter is used to split signals in the horizontal direction.

[0183] In one alternative implementation, there is a first phase difference between the transmitted signals of adjacent antennas in the horizontal direction among the M antennas, and a second phase difference between the transmitted signals of adjacent antennas in the vertical direction among the M antennas.

[0184] In one alternative implementation, 1 minute M h The splitter is used to split signals horizontally, 1 to M v When the splitter is used to split signals in the vertical direction, the first phase difference is determined based on the wavelength of the first total signal, the first transmission distance difference ΔL1 and the third transmission distance difference ΔL3, and the second phase difference is determined based on the wavelength of the first total signal, the second transmission distance difference ΔL2 and the fourth transmission distance difference ΔL4.

[0185] In one alternative implementation, the first transmission distance difference ΔL1, the second transmission distance difference ΔL2, the third transmission distance difference ΔL3, and the fourth transmission distance difference ΔL4 are all greater than or equal to zero, but not all of them are zero at the same time.

[0186] In one optional implementation, the processing module 1501 is specifically used for combining the M-path second sub-signals and the M-path fourth sub-signals in a one-to-one correspondence:

[0187] M h The j-th sub-signal after splitting the i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v -j+1 path fourth sub-signal combiner, where i is from 1 to M h positive integers, j being 1 to M h A positive integer; where M is a positive integer. h The first sub-signal of the i-th path in the first sub-signal of the (i-1)-th path transmits a first transmission distance difference ΔL1, M more than the first sub-signal of the (i-1)-th path. h The i-th sub-signal of the third path transmits a third transmission distance difference ΔL3 M more than the (i-1)-th sub-signal. v The j-th sub-signal of the second sub-signal transmits a second transmission distance difference ΔL2 M more than the (j-1)-th sub-signal. v The j-th sub-signal of the fourth sub-signal in the path has a transmission distance difference ΔL4 that is greater than that of the (j-1)-th sub-signal.

[0188] The specific descriptions of the transceiver module and processing module shown in the above embodiments are merely examples. For the specific functions or execution steps of the transceiver module and processing module, please refer to the above method embodiments, which will not be described in detail here.

[0189] The communication device according to the embodiments of this application has been described above. The following describes possible product forms of the communication device. Any product possessing the functions of the communication device shown in FIG15 above falls within the protection scope of the embodiments of this application.

[0190] The following description is merely an example and does not limit the product form of the communication device in the embodiments of this application to this.

[0191] In one possible implementation, in the communication device shown in FIG15, the processing module 1501 may be one or more processors. Optionally, the operation of the modulation module 1503 may also be performed in the processing module. The transceiver module 1502 may be a transceiver, or the transceiver module 1502 may also be a transmitting module and a receiving module. The transmitting module may be a transmitter, and the receiving module may be a receiver. The transmitting module and the receiving module are integrated into a single device, such as a transceiver. In the embodiments of this application, the processor and the transceiver may be coupled, etc. The connection method between the processor and the transceiver is not limited in the embodiments of this application.

[0192] As shown in Figure 16, the communication device 160 includes one or more processors 1620 and transceivers 1610. Exemplarily, the transceiver 1610 is used to perform the functions or steps implemented by the transceiver module 1502 shown in Figure 15, and the processor 1620 is used to perform the functions or steps implemented by the processing module 1501 and modulation module 1503 shown in Figure 15. Detailed descriptions of the processor 1620 and transceiver 1610 can be found in Figure 15 or the method embodiments shown above, and will not be elaborated further here.

[0193] The descriptions of the relevant steps and information in the above embodiments can be found in the descriptions of the method embodiments above, and will not be detailed here.

[0194] In various implementations of the communication device shown in Figure 16, the transceiver may include a receiver for performing a receiving function (or operation) and a transmitter for performing a transmitting function (or operation). The transceiver is also used to communicate with other devices / appliances via a transmission medium.

[0195] Optionally, the communication device 160 may further include one or more memories 1630 for storing program instructions and / or data. The memory 1630 is coupled to the processor 1620. The coupling in this embodiment is an indirect coupling or communication connection between devices, units, or modules, which can be electrical, mechanical, or other forms, for information exchange between devices, units, or modules. The processor 1620 may operate in conjunction with the memory 1630. The processor 1620 can execute program instructions stored in the memory 1630. Optionally, at least one of the above-mentioned memories may be included in the processor.

[0196] This embodiment does not limit the specific connection medium between the transceiver 1610, processor 1620, and memory 1630. In Figure 16, the memory 1630, processor 1620, and transceiver 1610 are connected via a bus 1640, which is represented by a thick line. The connection methods between other components are merely illustrative and not intended to be limiting. Buses can be categorized as address buses, data buses, control buses, etc. For ease of illustration, only one thick line is used in Figure 16, but this does not imply that there is only one bus or one type of bus.

[0197] In the embodiments of this application, the processor may be a general-purpose processor, a digital signal processor, an application-specific integrated circuit (ASIC), a field-programmable gate array (FPGA), or other programmable logic devices, discrete gate or transistor logic devices, discrete hardware components, etc., and can implement or execute the various methods, steps, and logic block diagrams disclosed in the embodiments of this application. The general-purpose processor may be a microprocessor or any conventional processor. The steps of the methods disclosed in the embodiments of this application can be directly manifested as being executed by a hardware processor, or being executed by a combination of hardware and software modules within the processor.

[0198] In this application embodiment, the memory may include, but is not limited to, non-volatile memory such as hard disk drive (HDD) or solid-state drive (SSD), random access memory (RAM), erasable programmable read-only memory (EPROM), read-only memory (ROM), or compact disc read-only memory (CD-ROM), etc. Memory is any storage medium capable of carrying or storing program code having instruction or data structure forms, and capable of being read and / or written by a computer (such as the communication device shown in this application), but is not limited to this. The memory in this application embodiment may also be a circuit or any other device capable of implementing storage functions, used to store program instructions and / or data.

[0199] Processor 1620 is primarily used to process communication protocols and signals, and / or control the entire communication device, execute software programs, and process data from those programs. Memory 1630 is primarily used to store software programs and data. Transceiver 1610 may include control circuitry and an antenna. The control circuitry is primarily used for converting baseband signals to radio frequency signals and processing radio frequency signals. The antenna is primarily used for transmitting and receiving radio frequency signals in the form of electromagnetic waves. Input / output devices, such as touchscreens, displays, and keyboards, are primarily used to receive user input data and output data to the user.

[0200] When the communication device is powered on, the processor 1620 can read the software program in the memory 1630, interpret and execute the instructions of the software program, and process the data of the software program. When data needs to be transmitted wirelessly, the processor 1620 performs baseband processing on the data to be transmitted and outputs the baseband signal to the radio frequency (RF) circuit. The RF circuit processes the baseband signal and transmits the RF signal outward in the form of electromagnetic waves through the antenna. When data is sent to the communication device, the RF circuit receives the RF signal through the antenna, converts the RF signal into a baseband signal, and outputs the baseband signal to the processor 1620. The processor 1620 converts the baseband signal into data and processes the data.

[0201] In another implementation, the radio frequency circuitry and antenna can be set up independently of the processor that performs baseband processing. For example, in a distributed scenario, the radio frequency circuitry and antenna can be arranged remotely, independent of the communication device.

[0202] The communication device shown in this application embodiment may also have more components than those in Figure 16, and this application embodiment does not limit this. The methods executed by the processor and transceiver shown above are only examples, and the specific steps executed by the processor and transceiver can be referred to the methods described above.

[0203] In another possible implementation, in the communication device shown in Figure 15, the processing module 1501 can be one or more logic circuits, and the transceiver module 1502 can be an input / output interface, or a communication interface, or an interface circuit, or an interface, etc. Alternatively, the transceiver module 1502 can also be a transmitting module and a receiving module. The transmitting module can be an output interface, and the receiving module can be an input interface. The transmitting module and the receiving module are integrated into one module, such as an input / output interface. As shown in Figure 17, the communication device shown in Figure 17 includes a logic circuit 1701 and an interface 1702. That is, the processing module 1501 can be implemented using the logic circuit 1701, and the transceiver module 1502 can be implemented using the interface 1702. The logic circuit 1701 can be a chip, a processing circuit, an integrated circuit, or a system-on-a-chip (SoC) chip, etc., and the interface 1702 can be a communication interface, an input / output interface, pins, etc. For example, Figure 17 uses the above-mentioned communication device as a chip, which includes the logic circuit 1701 and the interface 1702.

[0204] In this embodiment, the logic circuit and the interface can also be coupled to each other. The specific connection method of the logic circuit and the interface is not limited in this embodiment. For example, the logic circuit 1701 can be used to execute the functions or steps implemented by the processing module 1501 shown in FIG. 15, and the interface 1702 can be used to execute the functions or steps implemented by the transceiver module 1502 shown in FIG. 15. For a detailed description of the logic circuit 1701 and the interface 1702, please refer to FIG. 15 or the method embodiment shown above, which will not be detailed here.

[0205] The above description of the communication device is only an example. For a detailed description of the communication device shown in Figure 17, please refer to the above method embodiment or Figure 15 or Figure 16. It will not be described in detail here.

[0206] The communication device shown in the embodiments of this application can implement the method provided in the embodiments of this application in hardware form, or it can implement the method provided in the embodiments of this application in software form, etc., and the embodiments of this application do not limit it in this way.

[0207] The descriptions of relevant steps and information in the above embodiments can be found in the method embodiments described above, and will not be detailed here. For the specific implementation methods of the embodiments shown in Figure 17, please also refer to the above embodiments, which will not be detailed here.

[0208] In addition, this application also provides a computer program for implementing the operations and / or processes performed by various communication devices in the method provided in this application.

[0209] This application also provides a computer-readable storage medium storing computer code that, when executed on a computer, causes the computer to perform the operations and / or processes performed by various communication devices in the methods provided in this application.

[0210] This application also provides a computer program product comprising computer code or a computer program that, when run on a computer, causes the operations and / or processes performed by various entities in the method provided in this application to be executed.

[0211] In the embodiments provided in this application, it should be understood that the disclosed systems, apparatuses, and methods can be implemented in other ways. For example, the apparatus embodiments described above are merely illustrative; for instance, the division of modules is only a logical functional division, and in actual implementation, there may be other division methods. For example, multiple modules or components may be combined or integrated into another system, or some features may be ignored or not executed. Furthermore, the couplings or direct couplings or communication connections shown or discussed may be indirect couplings or communication connections through some interfaces, devices, or units, or they may be electrical, mechanical, or other forms of connection.

[0212] The modules described as separate components may or may not be physically separate. Similarly, the components shown as modules may or may not be physical modules; they may be located in one place or distributed across multiple network modules. Some or all of the modules can be selected to achieve the technical effects of the solutions provided in the embodiments of this application, depending on actual needs.

[0213] Furthermore, the functional modules in the various embodiments of this application can be integrated into one processing module, or each module can exist physically separately, or two or more modules can be integrated into one module. The integrated modules described above can be implemented in hardware or as software functional modules.

[0214] If the integrated module is implemented as a software functional module and sold or used as an independent product, it can be stored in a computer-readable storage medium. Based on this understanding, the technical solution of this application, in essence, or the part that contributes to the prior art, or all or part of the technical solution, can be embodied in the form of a software product. This computer software product is stored in a readable storage medium and includes several instructions to cause a computer device (which may be a personal computer, server, or network device, etc.) to execute all or part of the steps of the methods of the various embodiments of this application. The aforementioned readable storage medium includes various media capable of storing program code, such as USB flash drives, portable hard drives, read-only memory (ROM), random access memory (RAM), magnetic disks, or optical disks.

[0215] The above are merely specific embodiments of this application, but the scope of protection of this application is not limited thereto. Any variations or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in this application should be included within the scope of protection of this application. Therefore, the scope of protection of this application should be determined by the scope of the claims.

Claims

1. A communication method based on a hybrid beamforming (HBF) network, characterized in that, include: The first total signal is split into a first optical signal and a second optical signal. The first total signal includes N optical signals, which are signals obtained by using a first modulation method. The first modulation method includes using an electrical signal to drive the laser to change the output light intensity of the laser or using an external modulator to load an electrical signal onto the light field intensity or light field amplitude of the laser output. The first optical signal is input into the first HBF network to obtain M second sub-signals, wherein the M second sub-signals are obtained by processing the first optical signal through a 1-minute M-channel circuit. h The splitter is divided into M h After the first sub-signal of the road, it passes through M respectively. h 1 minute each v The result is obtained from the splitter, M = M h *M v ; The second optical signal is frequency-shifted and then input into the first HBF network to obtain M fourth sub-signals, wherein the M fourth sub-signals are obtained by frequency-shifting the second optical signal and then processing it for 1 minute. h The splitter is divided into M h After the third sub-signal of the road, it passes through M respectively. h 1 minute each v The result is obtained from the splitter; The M-channel second sub-signal and the M-channel fourth sub-signal are combined one-to-one and then output to M antennas after photoelectric conversion. The phase difference between any two adjacent electrical signals in the M electrical signals after photoelectric conversion is a constant.

2. The method according to claim 1, characterized in that: The M h There is a first transmission distance difference ΔL1 between any two adjacent first sub-signals in the first sub-signal of the path, and M after each first sub-signal is split v There is a second transmission distance difference ΔL2 between any two adjacent second sub-signals in the second sub-signal; The M h There is a third transmission distance difference ΔL3 between any two adjacent third sub-signals in the third sub-signal path, and M after each third sub-signal is split. v There is a fourth transmission distance difference ΔL4 between any two adjacent fourth sub-signals.

3. The method according to claim 1 or 2, characterized in that, The method of using an electrical signal to drive a laser to change the output light intensity of the laser includes: The bias current or bias voltage of a laser is driven by an electrical signal to change the output light intensity of the laser.

4. The method according to any one of claims 1-3, characterized in that, The process of applying an electrical signal to the light field intensity or amplitude output by the laser via an external modulator includes: An electrical signal is applied to the light field intensity output by the laser by using a Mach-Zehnder modulator or an electroabsorption modulator biased at the orthogonal point of light intensity. Alternatively, an electrical signal can be applied to the amplitude of the laser output light field by using a Mach-Zehnder modulator biased above the zero point of light intensity.

5. The method according to any one of claims 1-4, characterized in that: The 1 minute M h The splitter is used to split the signal in the horizontal direction, the 1M splitter v The splitter is used to split the signal in the vertical direction, or, the 1-splitter M h The splitter is used to split the signal in the vertical direction, the 1M splitter v A splitter is used to split signals in the horizontal direction.

6. The method according to claim 5, characterized in that: There is a first phase difference between the transmitted signals of adjacent antennas in the horizontal direction among the M antennas, and there is a second phase difference between the transmitted signals of adjacent antennas in the vertical direction among the M antennas.

7. The method according to claim 6, characterized in that: The 1 minute M h The splitter is used to split the signal in the horizontal direction, the 1M splitter v When the splitter is used to split the signal in the vertical direction, the first phase difference is determined based on the wavelength of the first total signal, the first transmission distance difference ΔL1 and the third transmission distance difference ΔL3, and the second phase difference is determined based on the wavelength of the first total signal, the second transmission distance difference ΔL2 and the fourth transmission distance difference ΔL4.

8. The method according to any one of claims 1-7, characterized in that, The first transmission distance difference ΔL1, the second transmission distance difference ΔL2, the third transmission distance difference ΔL3, and the fourth transmission distance difference ΔL4 are all greater than or equal to zero, but not all of them are zero at the same time.

9. The method according to any one of claims 1-8, characterized in that, The step of combining the M-channel second sub-signals with the M-channel fourth sub-signals in a one-to-one correspondence includes: M h The j-th sub-signal after splitting the i-th sub-signal of the first ... h The Mth sub-signal in the path h The Mth sub-signal after the third sub-signal of path -i+1 v -j+1 path fourth sub-signal combiner, where i is from 1 to M h positive integers, j being 1 to M v A positive integer; wherein, M h The first sub-signal of the i-th path in the first sub-signal of the path transmits a first transmission distance difference ΔL1 more than the first sub-signal of the (i-1)-th path, wherein M h The i-th sub-signal of the third sub-signal in the path is transmitted a third transmission distance difference ΔL3 more than the (i-1)-th sub-signal, and the M v The j-th sub-signal of the second sub-signal in the path j-1 transmits a second transmission distance difference ΔL2 more than the (j-1)-th sub-signal, wherein M v The j-th sub-signal of the fourth sub-signal in the path has a transmission distance difference ΔL4 that is greater than that of the (j-1)-th sub-signal.

10. A communication device, characterized in that, The communication device includes a module for performing the method as described in any one of claims 1-9; or, the communication device includes a processor for performing the method as described in any one of claims 1-9.

11. A communication device, characterized in that, It includes logic circuitry and an interface, the logic circuitry and the interface being coupled; the interface is used for inputting and / or outputting information, and the logic circuitry is used for performing the method as described in any one of claims 1-9.

12. A computer-readable storage medium, characterized in that, The computer-readable storage medium is used to store a computer program, which, when executed, performs the method as described in any one of claims 1-9.

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