Signal generation method and device, equipment and medium

Abstract

The invention provides a signal generation method and device and a communication system, and relates to the technical field of wireless communication and terminals. The method comprises the following steps: scattering a to-be-approximated binary keying signal OOK waveform generated based on a low-power wake-up LP-WUS signal to obtain to-be-processed waveforms with different phases; carrying out DFT (Discrete Fourier Transform) pre-coding or LS (Least Squares) optimization on the waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed; and obtaining a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal. According to the embodiment of the invention, the method can improve the frequency diversity gain and spectrum efficiency of the LP-WUS signal, improves the detection precision and detection efficiency of the LP-WUS signal, improves the receiving synchronism of NR, and reduces the energy loss.

Description

Technical Field

[0001] The present disclosure relates to the field of wireless communications and terminal technologies, and in particular to a signal generating method, device and communication system. Background Art

[0002] In the field of wireless communications, in the new radio (NR) system, when there is no data service, the terminal can enter a sleep state, such as an idle state (Idle) or an inactive state (Inactive), to reduce the power consumption level of the terminal and achieve the purpose of saving energy. When there is data service, the base station can wake up the terminal through a low-power wake-up signal (Low-Power Wake-Up Signal, LP-WUS), instructing the terminal to resume from the sleep state to the working state, such as the connected state, thereby completing the sending and receiving of data services.

[0003] At present, traditional NR reception is based on OFDM (Orthogonal Frequency Division Multiplexing) receivers, which demodulate LP-WUS signals through an accurate crystal oscillator or OFDM demodulator. However, the signal processing process of OFDM receivers, crystal oscillators, and OFDM demodulators is complex, which will result in high power consumption. When there are too many in-phase signals in the time domain of the waveform carrying the LP-WUS signal, it will cause spikes in the frequency domain. If a channel with strong frequency selectivity is encountered, once the spike falls into the deep attenuation area, the entire signal loses a lot of energy, and it is difficult to distinguish the LP-WUS signal, which reduces the detection accuracy and efficiency of the LP-WUS signal.

[0004] It should be noted that the information disclosed in the above background technology section is only used to enhance the understanding of the background of the present disclosure, and therefore may include information that does not constitute the prior art known to ordinary technicians in the field. Summary of the invention

[0005] The present disclosure provides a signal generation method, device and communication system, which at least to some extent overcome the problems of insufficient detection accuracy and low detection efficiency of LP-WUS signals caused by the difficulty in distinguishing LP-WUS signals in some cases in the related art.

[0006] Other features and advantages of the present disclosure will become apparent from the following detailed description, or may be learned in part by the practice of the present disclosure.

[0007] According to a first aspect of the present disclosure, there is provided a signal generating method, comprising:

[0008] The OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal is broken up to obtain waveforms to be processed with different phases;

[0009] Performing DFT transformation precoding or least squares LS optimization on waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed;

[0010] A target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal is acquired based on the frequency domain signal.

[0011] According to a second aspect of the present disclosure, there is provided a signal generating device, comprising:

[0012] A waveform processing module, used for breaking up the OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal to obtain a waveform to be processed with different phases;

[0013] An optimization module, used for performing DFT transformation precoding or least squares LS optimization on the waveform to be processed to obtain a frequency domain signal corresponding to the waveform to be processed;

[0014] The frequency domain processing module is used to obtain a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal.

[0015] According to a third aspect of the present disclosure, there is provided a communication system, including:

[0016] The base station is used to break up the OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal to obtain a waveform to be processed with different phases;

[0017] Performing DFT transformation precoding or least squares LS optimization on waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed;

[0018] Acquire a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal;

[0019] Acquire a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal, and generate a target transmission signal based on the frequency domain signal;

[0020] The user terminal includes a wake-up signal receiver and a main wireless module; the wake-up signal receiver is used to perform envelope detection on the received target transmission signal, obtain the LP-WUS signal, and wake up the main wireless module according to the LP-WUS signal; the main wireless module is used to communicate wirelessly with the base station.

[0021] According to a fourth aspect of the present disclosure, an electronic device is provided, including: a memory for storing instructions; and a processor for calling the instructions stored in the memory to implement the above-mentioned signal generation method.

[0022] According to a fifth aspect of the present disclosure, there is provided a computer-readable storage medium on which computer instructions are stored, and the computer instructions implement the above-mentioned signal generation method when executed by a processor.

[0023] According to a sixth aspect of the present disclosure, a computer program product is provided. The computer program product stores instructions, and when the instructions are executed by a computer, the computer implements the above-mentioned signal generation method.

[0024] According to a seventh aspect of the present disclosure, there is provided a chip, comprising at least one processor and an interface;

[0025] An interface for providing program instructions or data to at least one processor;

[0026] At least one processor is used to execute program instructions to implement the above signal generating method.

[0027] The signal generation method, device and communication system provided by the embodiments of the present disclosure, after obtaining the low-power wake-up LP-WUS signal, generates an OOK waveform of a binary keying signal to be approximated based on the LP-WUS signal, and then uses a sequence with the same modulus value but different phase to break up the OOK waveform to be approximated, so as to obtain an OOK waveform to be approximated with the same modulus value but different phase, repeats and phase transforms the OOK waveform to be approximated to generate multiple waveforms to be processed with different phases, then performs DFT transform precoding or least squares LS optimization on the processed waveform to obtain the corresponding frequency domain signal, and finally obtains a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal. The signal generation method disclosed in the present disclosure can improve the frequency diversity gain and spectrum efficiency of the LP-WUS signal by repeating and phase transforming the OOK waveform to be approximated generated based on the LP-WUS signal, and performing frequency domain repeated mapping on the frequency domain signal corresponding to the waveform to be processed with different phases obtained by phase transformation, thereby improving the detection accuracy and detection efficiency of the LP-WUS signal, and improving the synchronization of NR reception and reducing energy consumption loss.

[0028] It is to be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the present disclosure. BRIEF DESCRIPTION OF THE DRAWINGS

[0029] The accompanying drawings, which are incorporated in and constitute a part of this specification, illustrate embodiments consistent with the present disclosure and, together with the description, serve to explain the principles of the present disclosure.

[0030] Obviously, the drawings described below are only some embodiments of the present disclosure, and a person skilled in the art can obtain other drawings based on these drawings without any creative work.

[0031] Figure 1 The system architecture diagram of the communication system to which the signal generation method is applied in the embodiment of the present disclosure is schematically shown.

[0032] Figure 2 The flowchart of the signal generating method in the embodiment of the present disclosure is schematically shown.

[0033] Figure 3 The schematic diagram shows the principle diagram of OFDM baseband signal processing in the embodiment of the present disclosure.

[0034] Figure 4 The method for acquiring waveforms to be processed with different phases in an embodiment of the present disclosure is schematically shown.

[0035] Figure 5 The flowchart of determining a sequence for performing phase rotation according to a phase change pattern that changes at a preset interval in an embodiment of the present disclosure is schematically shown.

[0036] Figure 6 The flowchart of determining a sequence for performing phase rotation according to a phase change pattern that changes at a preset interval in an embodiment of the present disclosure is schematically shown.

[0037] Figure 7 The signal interface diagram after phase rotation of the high potential waveform in the OOK waveform to be approximated based on the sequence determined by the preset interval amount 1 in the embodiment of the present disclosure is schematically shown.

[0038] Figure 8 The signal interface diagram after the phase rotation of the OOK waveform to be approximated based on the sequence determined by the preset interval amount 1 in the embodiment of the present disclosure is schematically shown.

[0039] Fig. 9 The signal interface diagram after phase rotation of a high potential waveform approaching an OOK waveform based on a sequence determined based on a preset interval amount 5 in an embodiment of the present disclosure is schematically shown.

[0040] Fig.10 The signal interface diagram after phase rotation of the high potential waveform in the OOK waveform to be approximated is schematically shown based on the sequence determined by the preset interval amount 1 and the preset repetition amount 2 in the embodiment of the present disclosure.

[0041] Fig.11 The schematic diagram shows a signal interface diagram after replacing the constant modulus sequence corresponding to each ON waveform with the same replacement rule in the embodiment of the present disclosure.

[0042] Fig.12 The schematic diagram shows a signal interface diagram after the constant modulus sequence corresponding to each ON waveform is replaced with different ones according to the preset replacement rule in the embodiment of the present disclosure.

[0043] Fig.13 A schematic diagram shows a signal interface diagram after a preset replacement rule in an embodiment of the present disclosure is replaced when some ON waveforms among a plurality of ON waveforms have the same constant modulus sequences corresponding to them.

[0044] Figures 14A-14D The interface diagram for performing equal-length interception of waveforms to be processed with different phases corresponding to an OFDM symbol in an embodiment of the present disclosure is schematically shown.

[0045] Fig.15 The structural diagram of the signal generating device in the embodiment of the present disclosure is schematically shown.

[0046] Fig.16 A structural block diagram of an electronic device in an embodiment of the present disclosure is shown. DETAILED DESCRIPTION

[0047] Example embodiments will be described more fully hereinafter with reference to the accompanying drawings.

[0048] It should be noted that example embodiments may be implemented in many forms and should not be construed as being limited to the examples set forth herein.

[0049] In the related technologies in this field, Release 18 proposes a new topic on power consumption optimization of terminal equipment - low-power wake-up signal LP-WUS, which aims to further reduce the power of monitoring paging during DRX (Discontinuous Reception) by designing simple modulation signals and simple receivers, so that UE can further save energy in the idle IDLE / inactive INACTIVE state without causing a large transmission delay, which is very beneficial for the deployment of UEs without sustainable energy sources in future vertical industries, such as sensors, alarms, etc.

[0050] In order to reduce the power consumption of UE, a main wireless module MR and a wake-up signal receiver separated from MR are provided in UE. MR is similar to the role of traditional NRUE, used for sending and receiving signals, and is in a closed or deep sleep state most of the time, with high power consumption, generally in the order of milliwatts (mW), while the power consumption of the wake-up signal receiver is lower, generally in the order of microwatts (μW) or even nanowatts (nW). When the wake-up signal receiver detects the wake-up signal, MR will be activated to implement the basic functions of UE, including radio resource management (RRM) measurement, paging, cell reselection and cell switching, as well as various application (app) layer functions.

[0051] Traditional NR reception is based on OFDM receivers. When demodulating, accurate crystal oscillators or OFDM demodulators are required for demodulation. The signal processing process is complex and will generate high power consumption. In order to reduce power consumption, simple modulation signals and simple receivers can be designed. Therefore, the LP-WUS signal sent by the base station is usually converted into a binary keying signal for transmission, such as OOK (On-Off Keying) or FSK (Frequency Shift Keying). Among them, OOK is more widely used. Compared with FSK, OOK can only use limited simple devices for envelope detection and does not require a crystal oscillator. Therefore, multi-carrier OOK technology is usually used to modulate the LP-WUS signal to generate an NR signal to better coexist with other NR signals.

[0052] There are four OOK schemes, namely OOK-Option 1, OOK-Option 2, OOK-Option 3 and OOK-Option 4. Among them, OOK-Option 4 is a pre-distortion method that pre-generates the waveform and then approaches the target waveform with the help of discrete Fourier transform DFT-like operations. It has the dual advantages of rate and performance. Since OOK-Option 4 is an approximation method, it can realize the arbitrary setting of the time domain waveform by setting the corresponding number of signals carried on each OFDM symbol, so as to achieve high rate and high performance of signal transmission.

[0053] However, the main problem with the spectrum generated by OOK-Option 4 is that in order to perfectly represent the "ON" waveform in the time domain, many continuous sampling points are required to generate the same "ON" input, and too many in-phase signals in the time domain will cause spikes in the frequency domain, and the frequency domain energy is too concentrated in the first half of the spectrum. Once encountering the common fast-fading channel scenario of 3GPP, such as TDL-C 300ns, most of the amount will be lost, causing the waveform at the receiving end to be completely distorted. Since the receiving end uses envelope detection, no matter how high the signal-to-noise ratio is, the decision device cannot distinguish between high-level waveforms and low-level waveforms, resulting in low detection accuracy and efficiency of LP-WUS signals. At the same time, the frequency domain energy in the second half of the spectrum is too low, and the overall contribution is very small, resulting in very low spectrum efficiency.

[0054] Before describing the technical solutions in the embodiments of the present disclosure in detail, the technical terms that may be involved in the embodiments of the present disclosure are first explained and illustrated.

[0055] (1) LP-WUS: Low-Power Wake-Up Signal, used to wake up the main radio module MR in the UE.

[0056] (2) OOK: On-Off Keying, also known as binary amplitude shift keying (2ASK), uses a unipolar non-return-to-zero code sequence to control the on and off of a sinusoidal carrier.

[0057] (3) OOK-Option 4: A scheme for performing OOK modulation on the LP-WUS signal. It is a pre-distortion method that pre-generates a waveform and then approaches the target waveform through discrete Fourier transform or least squares optimization.

[0058] (4) DFT transform: Discrete Fourier Transform is the most basic method of signal analysis. It transforms the signal from the time domain to the frequency domain, and then studies the spectral structure and change law of the signal.

[0059] (5)LS optimization: Least Square, least squares optimization method.

[0060] (6) IFFT transform: Inverse Fast Fourier Transform, inverse fast Fourier transform.

[0061] After introducing the technical terms that may be involved in the embodiments of the present disclosure, the signal generating method in the present disclosure is described in detail.

[0062] Figure 1The system architecture block diagram of a communication system applying the technical solution of the present disclosure is schematically shown.

[0063] like Figure 1 As shown, the system architecture 100 of the communication system may include a base station 101, an NR terminal 102 and a network, wherein the base station 101 is used to break up the OOK waveform of the binary keying signal to be approximated generated based on the low-power wake-up LP-WUS signal to obtain a waveform to be processed with different phases; perform DFT transform precoding or least squares LS optimization on the waveform to be processed with different phases to obtain a frequency domain signal corresponding to the waveform to be processed; obtain a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal; obtain a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal, and generate a target transmission signal based on the frequency domain signal; the wake-up signal receiver in the NR terminal 102 is used to receive a target transmission signal transmitted through a multipath fading channel, demodulate and envelope detect the received target transmission signal, obtain the LP-WUS signal, and send the LP-WUS signal to the main wireless module in the NR terminal 102 to wake up the main wireless module; the network is a communication network, which is used to provide a data transmission link between the base station 101 and the NR terminal 102.

[0064] The technical solution provided by the embodiments of the present disclosure can be applied to a base station, which generates an LP-WUS signal and performs modulation, phase rotation, time-frequency conversion, frequency domain repetition mapping and other processing on the LP-WUS signal.

[0065] The signal generation method in the present disclosure can be applied to any scenario involving generating an LP-WUS signal and using the LP-WUS signal to wake up the main wireless module. The signal generation method provided by the present disclosure is described in detail below in conjunction with specific implementations.

[0066] Figure 2 A flow chart of a signal generation method is shown, the method is applied to a base station, the base station may be Figure 1 The base station 101 in Figure 2 As shown, the signal generating method includes steps S220-S260.

[0067] In S220, the waveform of the binary keying signal OOK to be approximated generated based on the low power wake-up LP-WUS signal is broken up to obtain waveforms to be processed with different phases.

[0068] In S240, DFT transform precoding or least squares LS optimization is performed on the waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed.

[0069] In S260, a target frequency domain signal having the same frequency domain bandwidth as that of the LP-WUS signal is acquired based on the frequency domain signal.

[0070] The signal generation method provided by the embodiment of the present disclosure generates an OOK waveform of a binary keying signal to be approximated based on the LP-WUS signal after acquiring a low-power wake-up LP-WUS signal, and then uses a sequence with the same modulus value but different phase to break up the OOK waveform to be approximated to obtain an OOK waveform to be approximated with the same modulus value but different phase, repeats and transforms the phase of the OOK waveform to be approximated to generate multiple waveforms to be processed with different phases, then performs DFT transform precoding or least squares LS optimization on the processed waveform to obtain a corresponding frequency domain signal, and finally obtains a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal. On the one hand, the signal generation method disclosed in the present invention can obtain a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal by repeating and phase-shifting the OOK waveform to be approximated based on the LP-WUS signal, and performing frequency domain repeated mapping according to the frequency domain signal corresponding to the waveform to be processed after the phase shift, thereby improving the frequency diversity gain of the LP-WUS signal, so that when the LP-WUS signal passes through a frequency selective fading channel, at least one peak is not affected and has an envelope that can be distinguished from noise, thereby ensuring that the receiving end can detect the LP-WUS signal through envelope detection; on the other hand, it ensures that the wake-up signal receiver can wake up the MR in time to meet the needs of power saving design.

[0071] In the field of 5G and 5G+ mobile communications, signals are usually transmitted in a multi-carrier waveform, and the multi-carrier waveform is usually implemented based on the orthogonal frequency division multiplexing technology OFDM. OFDM is a type of multi-carrier modulation, which realizes parallel transmission of high-speed serial data through frequency division multiplexing. It has good resistance to multipath fading and can support multi-user access. Therefore, before describing the signal generation method in the present disclosure in detail, the orthogonal frequency division multiplexing technology OFDM is briefly described first.

[0072] Figure 3 The schematic diagram of OFDM baseband signal processing is shown as follows: Figure 3As shown: The signal processing flow is divided into the signal processing flow of the transmitting end (base station) and the signal processing flow of the receiving end (UE): At the transmitting end, the bit stream is first modulated by QAM or QPSK, and then sequentially undergoes serial-to-parallel conversion and IFFT conversion, and then the parallel data is converted into serial data, and a protection interval (also known as "cyclic prefix") is added to form an OFDM code element. When framing, a synchronization sequence and a channel estimation sequence need to be added so that the receiving end can perform burst detection, synchronization and channel estimation, and finally output an orthogonal baseband signal; at the receiving end, when the signal arrives, synchronization and channel estimation are first performed. After completing time synchronization, fractional frequency offset estimation and correction, the FFT transformation is performed, and integer frequency offset estimation and correction are performed. At this time, the data obtained is QAM or QPSK modulated data. Finally, the data is demodulated accordingly to obtain a bit stream.

[0073] In the exemplary embodiments of the present disclosure, the essence of performing serial-to-parallel conversion on the LP-WUS signal is to divide the LP-WUS signal into multiple signal blocks. Specifically, the division can be performed according to the number of bits carried by each OFDM symbol. After the serial-to-parallel conversion is completed, each signal block can be expanded in the time domain, and OOK modulation can be performed according to the OOK-Option 4 scheme to generate an OOK waveform to be approximated. The OOK waveform to be approximated is then repeated and phase-transformed. The multiple waveforms to be processed with different phases are then subjected to time-frequency transformation to obtain corresponding frequency domain signals. Finally, a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal is obtained based on all frequency domain signals, and the target frequency domain signal is mapped to the corresponding RE in the OFDM modulator. This is Figure 3 The modulation mapping process shown in FIG. Considering that at the transmitter, when the OOK-Option4 scheme is used to perform OOK modulation on the bit stream, many continuous sampling points are required to generate the same "ON" input to generate a perfect "ON" waveform in the time domain. However, too many in-phase signals in the time domain will cause spikes in the frequency domain. When encountering a channel with strong frequency selectivity, once the spike falls into the deep attenuation area, the entire signal loses a lot of energy, and it is difficult to distinguish it by the envelope detection method. Therefore, by repeating and phase-changing the approximate OOK waveform in the modulation mapping process to form multiple waveforms with different phases to be processed, the frequency domain signals corresponding to the multiple waveforms with different phases to be processed are spliced ​​to obtain the target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal, ensuring that as long as not all bandwidths are located at the deep attenuation point of the channel, at least one frequency domain peak can be guaranteed to be unaffected and have an envelope that can be distinguished from noise, thereby ensuring that the signal finally sent to the receiver has a high frequency diversity gain, and can still have good performance when passing through a frequency selective fading channel, thereby improving the detection rate of the LP-WUS signal.

[0074] In the above embodiment, if Figure 4 As shown, S220 breaks up the waveform of the binary keying signal OOK to be approximated generated based on the low power wake-up LP-WUS signal to obtain waveforms to be processed with different phases, which may include steps S401-S404.

[0075] In S401, an OOK waveform to be approximated is generated based on the LP-WUS signal;

[0076] In S402, a sequence with the same modulus value but different phase is used to break up the OOK waveform to be approximated, thereby obtaining an OOK waveform with the same modulus value but different phase.

[0077] In S403, the OOK waveform to be approximated with the same modulus value but different phases is repeated according to a preset number to generate a plurality of OOK waveforms to be processed;

[0078] In S404, phase transformation is performed on each OOK waveform to be processed according to different frequency domain mapping positions to obtain a plurality of waveforms to be processed with different phases.

[0079] Among them, in step S401, the OOK waveform to be approximated is generated based on the LP-WUS signal, which can be specifically implemented according to the following method: first, the number of bits contained in the LP-WUS signal is rate matched according to the number of bits that can be carried by an orthogonal frequency division multiplexing OFDM symbol, so as to divide the LP-WUS signal into multiple signal blocks; then, each signal block is time-domain expanded and OOK modulated to obtain the OOK waveform to be approximated corresponding to each signal block. Specifically, when the LP-WUS signal is divided into multiple signal blocks, the number of bits contained in the LP-WUS signal is rate matched according to the number of bits that can be carried by each OFDM symbol. For example, the bit stream corresponding to the LP-WUS signal is b(0), b(1), ..., b(M bit -1), the number of bits contained is M bit , the number of bits that each OFDM symbol can carry is Then we can generate signal blocks, i.e. Each of them is a signal block, and these signal blocks are processed in parallel during the modulation mapping process. Since the processing flow of each signal block is the same, in the embodiment of the present disclosure, only the modulation processing flow of one signal block is described.

[0080] In an exemplary embodiment of the present disclosure, after acquiring a signal block, the signal block may be time-domain expanded and OOK modulated to generate an OOK waveform to be approximated. When the signal block is time-domain expanded, it may be expanded according to the number of sampling points required for subsequent time-frequency conversion of the waveform to be processed. In an embodiment of the present disclosure, after the OOK waveform to be approximated is repeated and phase-transformed to obtain a plurality of waveforms to be processed with different phases, DFT transform precoding or LS optimization is used to process each waveform to be processed, so the signal block may be time-domain expanded according to the number of DFT sampling points and the number of LS optimization sampling points.

[0081] When the DFT sampling point number is used for expansion, the sampling point number can be set to the frequency domain bandwidth size of the LP-WUS signal. This can avoid the need to intercept the frequency domain signal according to the frequency domain bandwidth size of the LP-WUS signal after completing the DFT change precoding. When the frequency domain bandwidth size of the LP-WUS signal is smaller than the maximum number of carrying bits corresponding to the OFDM symbol, the portion of the OFDM symbol not covered by the extended signal is filled with zeros.

[0082] When LS optimized sampling points are used for expansion, the sampling points can be set to any value greater than the frequency domain bandwidth of the LP-WUS signal and less than or equal to the maximum number of bits carried by the OFDM symbol. For example, FFT sampling points can be used for expansion to fill the signal bits in the OFDM symbol, or other sampling points can be selected to perform time domain expansion on the signal block. When the signal bits in the OFDM symbol are not filled, zeros are still used to fill the part of the OFDM symbol not covered by the extended signal.

[0083] In an exemplary embodiment of the present disclosure, when a signal block is time-domain expanded, each bit in the signal block is expanded by the same multiple, for example, one OFDM symbol is allocated to bits, the number of sampling points to be expanded is Then each bit needs to be expanded to In the embodiment of the present disclosure, the extended signal block is marked as For ease of understanding, an example is used to illustrate that when a signal block allocated to an OFDM symbol is 1101, and you want to expand the signal block to the LP-WUS signal bandwidth size of 72, then each bit needs to be expanded to 18 bits, that is, the extended signal block is composed of 18 1s, 18 1s, 18 0s and 18 1s in sequence.

[0084] After obtaining the extended signal block, the extended signal block can be modulated using the OOK-Option 4 scheme to generate an OOK waveform to be approximated corresponding to the extended signal block. It is worth noting that since one signal block corresponds to one OFDM symbol, the OOK waveform to be approximated corresponding to the signal block also corresponds to one OFDM symbol.

[0085] In an exemplary embodiment of the present disclosure, in order to enable a target transmission signal generated based on the LP-WUS signal to have good performance when passing through a frequency selective fading channel, and to ensure that the receiving UE can detect the LP-WUS signal by means of envelope detection, in an embodiment of the present disclosure, multiple waveforms to be processed with different phases corresponding to the OOK waveform to be approximated can be obtained, and frequency domain repeated mapping can be performed according to the frequency domain signals corresponding to the multiple waveforms to be processed, so that the target frequency domain signal includes multiple frequency domain peak signals corresponding to the OOK waveform to be approximated. Then, as long as not all bandwidths are located in the deep attenuation region of a channel with strong frequency selectivity, there will be at least one frequency domain peak signal that will not be affected and has an envelope that can be distinguished from noise, thereby ensuring that the receiving UE can detect the LP-WUS signal by means of envelope detection.

[0086] In some embodiments, S402 uses a sequence with the same modulus value but different phase to break up the OOK waveform to be approximated, and obtains an OOK waveform to be approximated with the same modulus value but different phase. It can be that a sequence including multiple phase rotation factors with the same modulus value and phases changing according to a preset change rule is used to perform phase rotation on the OOK waveform to be approximated, and the OOK waveform to be approximated with the same modulus value but different phase is obtained.

[0087] S402 uses a sequence with the same modulus value but different phase to break up the OOK waveform to be approximated, and obtains an OOK waveform to be approximated with the same modulus value but different phase. It can also use a constant modulus sequence to replace the high-level ON waveform of the OOK waveform to be approximated, and obtain an OOK waveform to be approximated with the same modulus value but different phase. The constant modulus sequence is a group of sequences with the same modulus value but different phases.

[0088] The following first introduces a scheme for performing phase rotation on the OOK waveform to be approximated by using a sequence of phase rotation factors having the same modulus and whose phases change according to a preset change rule to obtain the OOK waveform to be approximated.

[0089] In an exemplary embodiment of the present disclosure, when the LP-WUS signal is serial-to-parallel converted to generate a plurality of signal blocks, the number of bits contained in the LP-WUS signal is rate matched according to the number of bits that each OFDM symbol can carry. For example, the bit stream corresponding to the LP-WUS signal is b(0), b(1), ..., b(M bit -1), the number of bits contained is Mbit , the number of bits that each OFDM symbol can carry is Then we can generate signal blocks, i.e. Each of them is a signal block, and these signal blocks are processed in parallel during the modulation mapping process. Since the processing flow of each signal block is the same, in the embodiment of the present disclosure, only the processing flow of one signal block is described.

[0090] In an exemplary embodiment of the present disclosure, after acquiring a signal block, the signal block may be time-domain expanded and OOK modulated to generate an OOK waveform to be approximated. When the signal block is time-domain expanded, it may be expanded according to the number of sampling points corresponding to the method of performing time-frequency conversion on the waveform after the phase rotation. In an embodiment of the present disclosure, after the OOK waveform to be approximated is phase-rotated, DFT transform precoding or LS optimization is used to process the OOK waveform to be approximated with the same modulus value but different phase, so the signal block may be time-domain expanded according to the number of DFT sampling points and the number of LS optimization sampling points. When DFT sampling points are used for expansion, the sampling points can be set to the LP-WUS signal bandwidth size, so that after completing the DFT change precoding, the frequency domain signal needs to be intercepted according to the LP-WUS signal bandwidth size. When the LP-WUS signal bandwidth size is less than the maximum number of carrying bits corresponding to the OFDM symbol, the part of the OFDM symbol not covered by the extended signal is filled with zeros; when LS optimized sampling points are used for expansion, the sampling points can be set to any value greater than the LP-WUS signal bandwidth size and less than or equal to the maximum number of carrying bits of the OFDM symbol. For example, FFT sampling points can be used for expansion to fill the signal bits in the OFDM symbol, or other sampling points can be selected to perform time domain expansion on the signal block. When the signal bits in the OFDM symbol are not filled, zeros are still used to fill the part of the OFDM symbol not covered by the extended signal.

[0091] In an exemplary embodiment of the present disclosure, when a signal block is time-domain expanded, each bit in the signal block is expanded by the same multiple, for example, one OFDM symbol is allocated to bits, the number of sampling points to be expanded is Then each bit needs to be expanded to In the embodiment of the present disclosure, the extended signal block is marked as For ease of understanding, an example is used to illustrate that when a signal block allocated to an OFDM symbol is 1101, and you want to expand the signal block to the LP-WUS signal bandwidth size of 72, then each bit needs to be expanded to 18 bits, that is, the extended signal block is composed of 18 1s, 18 1s, 18 0s and 18 1s in sequence.

[0092] After obtaining the extended signal block, the extended signal block can be modulated using the OOK-Option 4 scheme to generate an OOK waveform to be approximated corresponding to the extended signal block. It is worth noting that since one signal block corresponds to one OFDM symbol, the OOK waveform to be approximated corresponding to the signal block also corresponds to one OFDM symbol.

[0093] In an exemplary embodiment of the present disclosure, the frequency diversity gain of the LP-WUS signal can be improved by performing phase rotation on the OOK waveform to be approximated. Specifically, a sequence of phase rotation factors having the same modulus and phases changing in a preset rule can be used to perform phase rotation on the OOK waveform to be approximated, so as to generate an OOK waveform to be approximated with the same modulus but different phases.

[0094] Since one OOK waveform to be approximated corresponds to one OFDM symbol, accordingly, the sequence used to perform phase rotation on the OOK waveform to be approximated also corresponds to the OFDM symbol, and the sequences corresponding to different OFDM symbols may be the same or different. In an embodiment of the present disclosure, the sequence can be constructed based on a phase rotation factor generated with different phase change modes, wherein the different phase change modes are: the phase changes at a preset interval, or the phase is partially repeated and the phase of the non-repeating part changes at a preset interval. Next, the construction method of the sequence for performing phase rotation on the OOK waveform to be approximated is described in detail.

[0095] (1) Phase changes at preset intervals

[0096] Figure 5 The flowchart of determining a sequence for performing phase rotation according to a phase change pattern that changes at a preset interval is schematically shown. Figure 5 As shown, the process at least includes steps S501 to S502, specifically:

[0097] In step S501, a variation sequence is determined according to a preset number of sampling points, the preset interval and a parameter corresponding to the OFDM symbol, and a modulo remainder operation is performed on the variation sequence and a phase rotation parameter to obtain a phase rotation coefficient sequence.

[0098] In an exemplary embodiment of the present disclosure, an initial variation sequence may be first determined according to a preset number of sampling points and a preset interval, wherein the preset number of sampling points is less than or equal to any positive integer, further, the preset number of sampling points can be the number of sampling points of the corresponding ON waveform in the OOK waveform to be approximated or the number of sampling points in the OOK waveform to be approximated; the preset interval can be any positive integer, for example, it can be 1, 2, 3, etc. When the preset interval is 1, it indicates that the phase changes continuously, and when the preset interval is greater than 1, it indicates that the phase changes at intervals; the parameter corresponding to the OFDM symbol is used to adjust the phase rotation factor in the sequence, thereby realizing the phase adjustment of each signal in the extended signal block. In the embodiments of the present disclosure, the parameters corresponding to different OFDM symbols may be the same or different. Specifically, when the indexes of the OFDM symbols are different, the parameters corresponding to each OFDM symbol may be set to 0; when the indexes of the OFDM symbols are different, the parameters corresponding to each OFDM symbol may be set to be the same as the index of the OFDM symbol; for example, when the OFDM symbol is 1, the parameter is 1, when the OFDM symbol is 3, the parameter is 3, and so on; or, when the indexes of the OFDM symbols are different, the parameters corresponding to each OFDM symbol may be set to any different values, for example, when the OFDM symbol is 1, the parameter is 2, when the OFDM symbol is 2, the parameter is 4, and so on. By setting different parameters for different OFDM symbols, different phase conversions can be performed on the signals in the extended signal blocks corresponding to different OFDM symbols, further avoiding the frequency domain peaks caused by the same phase concentration, and thus improving the frequency diversity gain of the LP-WUS signal.

[0099] For the convenience of description, the preset number of sampling points is marked as N, the preset interval is marked as p, and the parameter corresponding to the OFDM symbol is marked as r. Then, according to the preset number of sampling points and the preset interval, an initial variation sequence m can be obtained. i ={0, p, ..., p(N-1)}, where i is the index corresponding to the variation, N and p are positive integers. Further, the variation sequence can be obtained according to the initial variation sequence and the parameters corresponding to the OFDM symbol as (m i +r).

[0100] After obtaining the variation sequence, a modulo remainder operation can be performed on the variation sequence and the phase rotation parameter to obtain a phase rotation coefficient sequence. Similarly, the phase rotation parameter can be marked as μ, and the phase rotation coefficient sequence can be obtained as follows: The phase rotation parameter μ may be any positive number. Furthermore, the phase rotation parameter may also be a value determined according to a method for determining a preset number of sampling points. Specifically, when the preset number of sampling points is the number of sampling points corresponding to the ON waveform in the OOK waveform to be approximated, When the preset number of sampling points is the number of sampling points in the OOK waveform to be approximated, in, is the number of bits contained in the extended signal block corresponding to the OFDM symbol, It is the number of bits carried by one OFDM symbol during rate matching.

[0101] In step S502, is a phase rotation base, generates a plurality of phase rotation factors according to the phase rotation base and the phase rotation coefficient sequence, and constructs the sequence according to the phase rotation factors.

[0102] In an exemplary embodiment of the present disclosure, after determining the phase rotation coefficient sequence, multiple phase rotation factors can be generated according to the phase rotation basis and the phase rotation coefficient sequence, and then a sequence for performing phase rotation on the approximated OOK waveform can be constructed according to the multiple phase rotation factors, wherein the phase rotation basis is The constructed sequence is as shown in expression (1):

[0103]

[0104] Among them, α l (m i ) is the sequence; l is the index of the OFDM symbol; m i +r is the variation sequence; i is the variation index, which is a non-negative integer; N is the preset number of sampling points, which is an arbitrary positive integer; r is the parameter corresponding to the OFDM symbol, which is a non-negative integer; μ is the phase rotation parameter, which is an arbitrary positive number; p is the preset interval; m i modμ is the phase rotation coefficient sequence.

[0105] (2) The phase part repeats and the phase of the non-repeating part changes at a preset interval

[0106] Figure 6 The flowchart of determining a sequence for performing phase rotation according to a phase change pattern that changes at a preset interval is schematically shown. Figure 6 As shown, in step S601, a variation sequence is determined according to a preset number of sampling points, the preset interval and a parameter corresponding to the OFDM symbol, and a modulo remainder operation is performed on the variation sequence and the phase rotation parameter to obtain a phase rotation coefficient sequence; in step S602, is a phase rotation base, generates multiple phase rotation factors according to the phase rotation base and the phase rotation coefficient sequence, and constructs an initial sequence according to the phase rotation factors; in step S503, the phase rotation factors to be repeated in the initial sequence are repeated according to a preset repetition amount to obtain the sequence.

[0107] contrast Figure 5 and Figure 6It can be seen that the initial sequence is a sequence obtained when the phase changes at a preset interval. As shown in expression (1), the final sequence used to perform phase rotation on the approximated OOK waveform can be obtained by repeating part of the phase rotation factors to be repeated in the initial sequence. In the embodiment of the present disclosure, the number of phase rotation factors to be repeated is less than the number of phase rotation factors included in the initial sequence. At the same time, the preset repetition amount does not exceed half of the total signal amount in the extended signal block corresponding to the OFDM symbol. The specific value can be set according to actual needs, and the embodiment of the present disclosure does not make specific limitations on this.

[0108] According to expression (1), the sequence constructed with multiple phase rotation factors can also be expressed as expression (2):

[0109]

[0110] Exemplarily, when the phase rotation factors to be repeated are the phase rotation factors of the 0th and 1st positions, the sequence can be converted into expression (3):

[0111]

[0112] Wherein, M is a preset repetition amount and is a positive integer greater than 1.

[0113] In an exemplary embodiment of the present disclosure, after determining a sequence containing multiple phase rotation factors according to different phase change patterns, the OOK waveform to be approximated corresponding to the OFDM symbol can be phase rotated according to the sequence. Specifically, the phase rotation factors at different positions are applied to the signal in the extended signal block corresponding to the OFDM symbol to transform the signal.

[0114] From the perspective of waveform transformation, the phase rotation of the OOK waveform to be approximated can be performed by determining the waveform to be rotated corresponding to the preset number of sampling points in the OOK waveform to be approximated according to the method of determining the preset number of sampling points. For example, if the preset number of sampling points is determined according to the number of sampling points corresponding to the ON waveform, then the ON waveform can be used as the waveform to be rotated. For example, if the preset number of sampling points is determined according to the number of sampling points corresponding to the OOK waveform to be approximated, then the OOK waveform to be approximated can be used as the waveform to be rotated, and so on. Then, the waveform to be rotated is phase-rotated according to the phase rotation factor in the sequence to obtain a phase-rotated OOK waveform. Specifically, in mathematical operations, the signal matrix corresponding to the OOK waveform to be approximated is rotated using the phase rotation matrix corresponding to the sequence. If the phase rotation matrix is ​​marked as α μ , the signal matrix corresponding to the OOK waveform to be approximated is marked as b n , then the phase-rotated OOK waveform is α μ b n .

[0115] Since the phase rotation of the OOK waveform to be approximated is essentially the phase transformation of the signals constituting the OOK waveform to be approximated, from the perspective of signal transformation, when the OOK waveform to be approximated is phase rotated, the target phase rotation factor corresponding to the signal in the extended signal block corresponding to the OOK waveform to be approximated can be determined from a sequence containing multiple phase rotation factors, and then the signal is phase rotated according to the target phase rotation factor to obtain a phase rotated signal. After the traversal is completed, the phase rotated OOK waveform can be constructed according to all phase rotated signals. Specifically for mathematical operations, the extended signal block corresponding to the OFDM symbol indexed as l can be marked as For the signal in the extended signal block, the target phase rotation factor corresponding to it is determined from the sequence, and the target phase rotation factor is used to perform phase rotation on the corresponding signal, that is, according to Perform phase rotation, where i is the index of the signal in the extended signal block, j is the index of the phase rotation factor in the sequence, which is a non-negative integer. i and j can be the same or different. Then, the phase rotation signal block corresponding to the OFDM symbol can be obtained as follows: For the inclusion of M bit For the LP-WUS signal, the final phase rotation signal is

[0116] It is worth noting that when determining the target phase rotation factor corresponding to the signal, it can be determined according to the position index of the signal in the OFDM symbol, or a phase rotation factor whose position index in the sequence is different from the position index of the signal on the OFDM symbol can be used as the target phase rotation factor. For example, when the signal is the 0th bit signal on the OFDM symbol, the 0th bit phase rotation factor in the sequence can be used as the target phase rotation factor, or a non-0th bit phase rotation factor can be used as the target phase rotation factor, such as the 2nd bit, 4th bit, etc. The phase rotation factor is used as the target phase rotation factor.

[0117] Figure 7 The signal interface diagram after the phase rotation of the high potential waveform in the OOK waveform to be approximated is schematically shown based on the sequence determined by the preset interval 1, as shown in FIG. Figure 7 As shown, the extended signal block corresponding to one OFDM symbol is {1111000011110000}. Since the high potential waveform occupies 4 bits, the preset number of sampling points N=4 can be determined. When the phase rotation parameter When the parameter r corresponding to the OFDM symbol is 0, the sequence used for phase rotation can be obtained as According to this sequence, the high potential signal in the extended signal block can be phase rotated, and the final rotated signal block is:

[0118] Figure 8 The signal interface diagram after the phase rotation of the sequence to be approximated OOK waveform based on the preset interval 1 is schematically shown, as shown in FIG. Figure 8 As shown, the extended signal block corresponding to one OFDM symbol is {1111000011110000}. Since the extended signal block contains 16 bits, the preset number of sampling points N=16 can be determined. When the phase rotation parameter When the parameter r corresponding to the OFDM symbol is 1, the sequence used for phase rotation can be obtained as According to this sequence, the extended signal block can be phase rotated. Since the signal is 0, it is still 0 after rotation, so the rotated signal block can be obtained as

[0119] Fig. 9 The signal interface diagram after phase rotation of the high potential waveform approaching the OOK waveform based on the sequence determined by the preset interval 5 is schematically shown, as shown in FIG. Fig. 9 As shown, the extended signal block corresponding to one OFDM symbol is {1111000011110000}, then the preset number of sampling points N=4 can be determined. When the phase rotation parameter When the parameter r corresponding to the OFDM symbol is 3, the sequence used for phase rotation can be obtained as According to the sequence, the extended signal block can be phase rotated, and the rotated signal block can be obtained as follows:

[0120] Figure 1 0 schematically shows a signal interface diagram after the phase rotation of the high potential waveform in the OOK waveform to be approximated is performed based on the sequence determined by the preset interval amount 1 and the preset repetition amount 2, as shown in FIG. Figure 1 0, the extended signal block corresponding to one OFDM symbol is {1111000011110000}, then the preset number of sampling points N=4 can be determined. When the parameter r corresponding to the OFDM symbol is 0 and the phase rotation factors to be repeated are the phase rotation factors of the 0th and 1st positions, the sequence used for phase rotation can be obtained as According to the sequence, the high potential signal in the extended signal block can be phase rotated, and the rotation signal block can be obtained as follows:

[0121] It is worth noting that although the number of phase rotation factors in the sequence is greater than the number of sampling points corresponding to the high-potential waveform, when the signal corresponding to the high-potential waveform is phase rotated, it is only rotated according to the target phase rotation factor corresponding to the high-potential waveform signal in the sequence.

[0122] In an exemplary embodiment of the present disclosure, Figure 7-Figure 10 The phase rotation shown in the figure all uses the phase rotation factor and signal corresponding to the same position index to perform phase rotation. However, in the embodiment of the present disclosure, it is not limited to this. Phase rotation can also be performed according to phase rotation factors and signals with different position indexes. For example, the phase rotation factors in the sequence are cyclically shifted. When the number of phase rotation factors is greater than the number of signals in the waveform to be rotated, some of the phase rotation factors in the sequence can be used as target phase rotation factors corresponding to the signals in the waveform to be rotated. Fig. 9 For example, the first phase rotation factor in the sequence can be used as the target phase rotation factor corresponding to the 0th signal in the high-level signal, the second phase rotation factor can be used as the target phase rotation factor corresponding to the 1st signal in the high-level signal, the third phase rotation factor can be used as the target phase rotation factor corresponding to the 2nd signal in the high-level signal, and the fourth phase rotation factor can be used as the target phase rotation factor corresponding to the 3rd signal in the high-level signal. Finally, the rotation signal block is obtained as follows: When the number of phase rotation factors is the same as the number of signals, the 2nd phase rotation factor is used to phase rotate the 0th signal, then correspondingly, the 0th phase rotation factor is used to phase rotate the 2nd to last signal, and the 1st phase rotation factor is used to phase rotate the 1st to last (last) signal, and so on.

[0123] The following describes a solution in which a constant modulus sequence is used to replace the high-level ON waveform of the OOK waveform to be approximated in the above embodiment to obtain an OOK waveform to be approximated with the same modulus value but different phase. The similarities between this solution and the above embodiment are not repeated here.

[0124] In some embodiments, the constant modulus sequence includes one or more of the following sequences: a ZC sequence, a random orthogonal amplitude modulation sequence, a CGS sequence, and a low PAPR sequence. That is, the constant modulus sequence can be one of the above sequences, or a combination of the above sequences. Among them, the random orthogonal amplitude modulation sequence can be a sequence composed of BPSK or QPSK modulation symbols.

[0125] In some embodiments, a high-level ON waveform of the OOK waveform to be approximated is replaced by a constant modulus sequence to obtain a phase-rotated OOK waveform, including replacing the high-level ON waveform of the OOK waveform to be approximated by a constant modulus sequence based on a preset replacement rule to obtain a phase-rotated OOK waveform.

[0126] The preset replacement rules include that the constant modulus sequence corresponding to each ON waveform is the same, the constant modulus sequence corresponding to each ON waveform is different, and the constant modulus sequences corresponding to some ON waveforms among multiple ON waveforms are the same.

[0127] Fig.11 The schematic diagram shows that the preset replacement rule is that the constant modulus sequence corresponding to each ON waveform is the same, and the signal interface diagram after replacement is shown as follows Fig.11 As shown, the extended signal block corresponding to one OFDM symbol is {1111000011110000}, the high potential waveform occupies 4 bits, and the high potential waveform is replaced by the constant modulus sequence 1.

[0128] Fig.12 The schematic diagram shows that the preset replacement rule is that the constant modulus sequence corresponding to each ON waveform is different, and the signal interface diagram after replacement is shown as follows: Fig.12 As shown, the extended signal block corresponding to one OFDM symbol is {1111000011110000}, the high potential waveform occupies 4 bits, and the high potential waveform is replaced with different constant modulus sequences, that is, replaced with constant modulus sequence 1 and constant modulus sequence 2.

[0129] Fig.13 The schematic diagram shows that the preset replacement rule is that the constant modulus sequences corresponding to some ON waveforms in multiple ON waveforms are the same, and the signal interface diagram after replacement is shown, such as Fig.11 As shown, the extended signal block corresponding to one OFDM symbol is {11110000111100001111000011110000}, and the high potential waveform is replaced by two constant modulus sequences 1 and two constant modulus sequences 2.

[0130] For step S402, after obtaining the OOK waveform to be approximated, the OOK waveform to be approximated can be repeated according to a preset number to generate multiple OOK waveforms to be processed, that is, the number of OOK waveforms to be processed is equal to the preset number, and the OOK waveform to be processed is exactly the same as the OOK waveform to be approximated. Among them, the preset number can be set according to actual needs. The larger the preset number, the greater the frequency diversity gain. In the embodiment of the present disclosure, the preset number is an integer multiple of the frequency domain bandwidth size of the LP-WUS signal and does not exceed the frequency domain bandwidth size of the LP-WUS signal. It is worth noting that the preset number cannot be too large to prevent the subsequent interception of the frequency domain signal, so as to prevent the inability to fully obtain the part where the frequency domain energy is concentrated, thereby affecting the accuracy of the detection result of the receiving UE.

[0131] For step S403, after repeatedly obtaining multiple OOK waveforms to be processed for the approximated OOK waveform, each OOK waveform to be processed can be phase-transformed according to different frequency domain mapping positions to obtain multiple waveforms to be processed with different phases. When performing phase transformation, different OOK waveforms to be processed correspond to different starting frequency domain mapping positions, and the starting frequency domain mapping position is related to the index corresponding to the OOK waveform to be processed. Therefore, the starting frequency domain mapping position corresponding to each OOK waveform to be processed can be determined first, and then the phase transformation sequence corresponding to the OOK waveform to be processed can be determined according to the starting frequency domain mapping position. Finally, the corresponding OOK waveform to be processed is phase-transformed according to the phase transformation sequence to obtain the waveform to be processed.

[0132] In an exemplary embodiment of the present disclosure, when determining the starting frequency domain mapping position corresponding to each OOK waveform to be processed, the starting frequency domain mapping position corresponding to each OOK waveform to be processed can be determined according to the starting frequency domain mapping position corresponding to the OOK waveform to be processed with an index of 0, the index corresponding to each OOK waveform to be processed, the preset number for repeating the OOK waveform to be approximated, and the frequency domain bandwidth size of the LP-WUS signal. For example, when the preset number is Q, Q is a positive integer greater than 1, and the starting frequency domain mapping position corresponding to the OOK waveform to be processed with an index of 0 is kc, first, the OOK waveform to be approximated can be repeated according to the preset number Q to obtain Q OOK waveforms to be processed, and then the corresponding indexes can be set for the Q OOK waveforms to be processed. Specifically, they can be numbered in sequence in the order of 0, 1, 2…Q-1, and then the starting frequency domain mapping position corresponding to each OOK waveform to be processed can be determined according to the preset number, the starting frequency domain mapping position corresponding to the OOK waveform to be processed with an index of 0, the index of the OOK waveform to be processed, and the frequency domain bandwidth size of the LP-WUS signal. For example, for the OOK waveform to be processed with an index i, As the corresponding starting frequency domain mapping position, correspondingly, for the OOK waveform to be processed with index 1, the starting frequency domain mapping position is For the OOK waveform to be processed with index (Q-1), the starting frequency domain mapping position is Wherein R is the frequency domain bandwidth size of the LP-WUS signal. It is worth noting that the starting frequency domain mapping position in the present disclosure is any RE in the corresponding OFDM symbol.

[0133] After determining the starting frequency domain mapping position corresponding to each OOK waveform to be processed, the starting frequency domain mapping position, the phase transformation basis The phase shift factor corresponding to each bit is determined by the position index of each bit in each OOK waveform to be processed, and then the phase shift sequence corresponding to the OOK waveform to be processed is determined according to the phase shift factors corresponding to all bits in the OOK waveform to be processed. For example, when the position index of a bit in the OOK waveform to be processed is m (0≤m≤(N-1), N is the total number of bits contained in the OOK waveform to be processed), then the phase shift factor corresponding to the bit is

[0134] After obtaining the phase transformation factors corresponding to all bits in the OOK waveform to be processed with index i, all the phase transformation factors can be sorted according to the position index corresponding to each bit, and then the phase transformation sequence corresponding to the OOK waveform to be processed with index i is obtained, that is, i=0,1,…,(Q-1), m=0,1,…,(N-1), N is the total number of bits contained in the OOK waveform to be processed. The phase transformation sequence is expanded into a sequence form, that is: It is worth noting that the phase transformation factors in the phase transformation sequence corresponding to each waveform to be processed are continuous, but the phase transformation sequences corresponding to two adjacent waveforms to be processed are not continuous, but partially overlapped.

[0135] In an exemplary embodiment of the present disclosure, the corresponding OOK waveform to be processed can be phase-transformed according to a phase transformation sequence to obtain the waveform to be processed after phase transformation. Specifically, the phase transformation factor in the phase transformation sequence is applied to the bits with the same position index in the OOK waveform to be processed to obtain the waveform to be processed.

[0136] In the field of signal processing, the phase transformation of a waveform is realized based on mathematical operations. Different mathematical operations are used for different transformation dimensions. In the embodiments of the present disclosure, the phase transformation of the OOK waveform to be processed can be divided into waveform transformation dimensions and signal transformation dimensions. Accordingly, the mathematical operation corresponding to the waveform transformation dimension can use matrix-level operations, and the mathematical operation corresponding to the signal transformation dimension can use signal-level operations. Next, different transformation dimensions and corresponding mathematical operations are described in detail.

[0137] (1) Waveform transformation dimension

[0138] In an exemplary embodiment of the present disclosure, when a matrix-level phase transformation is performed on the OOK waveform to be processed according to the phase transformation sequence, the waveform to be processed, the phase transformation sequence and the OOK waveform to be processed satisfy the relationship (4):

[0139]

[0140] in, is the matrix representation of the waveform to be processed; is the phase change sequence corresponding to the i-th OOK waveform to be processed; is the matrix representation of the i-th OOK waveform to be processed; i is the index of the OOK waveform to be processed; R is the frequency domain bandwidth of the LP-WUS signal; Q is the number of OOK waveforms to be processed, which is a positive integer greater than 1; kc is the index of the starting frequency domain mapping position of the OOK waveform to be processed with index 0; is the phase transformation basis; N is the total number of bits contained in the OOK waveform to be processed.

[0141] It is worth noting that, since one OOK waveform to be approximated corresponds to one OFDM symbol, then multiple OOK waveforms to be processed formed by repeating the OOK waveform to be approximated also correspond to one OFDM symbol, so the phase transformation can be performed on multiple OOK waveforms to be processed corresponding to one OFDM symbol based on formula (4). When the LP-WUS signal is divided into Z (Z is a positive integer greater than 1) signal blocks according to the number of bits carried by an OFDM symbol, and the number of repetitions corresponding to each OOK waveform to be approximated is Q (Q is a positive integer greater than 1), then Z×Q operations can be performed according to formula (4) to obtain the waveforms to be processed corresponding to all OOK waveforms to be approximated.

[0142] (2) Signal transformation dimension

[0143] In an exemplary embodiment of the present disclosure, the phase transformation of the corresponding OOK waveform to be processed is performed according to the phase transformation sequence, which essentially applies the phase transformation factor in the phase transformation sequence to the signal in the extended signal block corresponding to the OFDM symbol to perform phase transformation on the signal.

[0144] When the phase transformation of the OOK waveform to be processed is performed at the signal level according to the phase transformation sequence, the waveform to be processed, the phase transformation sequence and the OOK waveform to be processed satisfy the relationship (5):

[0145]

[0146] in, is the signal in the waveform to be processed; is the signal in the OOK waveform to be processed; is the phase change sequence corresponding to the OFDM symbol with index l; i' is the position index corresponding to each signal on the OFDM symbol; is the number of bits contained in the extended signal block corresponding to an OFDM symbol; kc is the index of the starting frequency domain mapping position of the OOK waveform to be approximated with index 0.

[0147] In an exemplary embodiment of the present disclosure, after a plurality of processed OOK waveforms with different phases are obtained by performing phase transformation on the processed waveforms according to different phase transformation sequences, DFT transformation precoding or LS optimization can be performed on the processed waveforms to obtain frequency domain signals corresponding to the processed waveforms. Furthermore, a target transmission signal sent to the UE can be generated based on the frequency domain signal.

[0148] In an exemplary embodiment of the present disclosure, similar to the phase transformation of the processed OOK waveform, DFT transform precoding or LS optimization can also be divided into matrix-level operations and signal-level operations. Since matrix-level DFT transform precoding is a commonly used signal transformation method in the field, it is not described in detail in the embodiments of the present disclosure. Next, only the matrix-level LS optimization scheme, the signal-level DFT transform precoding scheme, and the signal-level LS optimization scheme are described in detail.

[0149] (1) Matrix-level LS optimization scheme

[0150] Before describing the LS optimization scheme in the embodiment of the present disclosure, the existing OOK waveform generation method based on LS optimization is briefly described first.

[0151] The OOK waveform generation based on LS optimization is divided into a non-shift-based basic generation method and a shift-based extended generation method. Among them, the LS-optimized approximate expression corresponding to the non-shift-based basic generation method is shown in formula (6):

[0152]

[0153] Among them, x LS is the frequency domain signal after LS optimization; F inv is the inverse Fourier transform matrix, G is the interception matrix, b n For the extended signal block.

[0154] Expanding the approximation after LS optimization, we get the expression shown in (7):

[0155]

[0156] Expression (7) is a very typical FFT transformation. Each element in the matrix is ​​constructed by different FFT orthogonal bases, so the final DFT transformation result will be obtained. At the same time, the truncation matrix G is composed of an L-long square matrix and all 0s, aiming to extract the elements of the target bandwidth length L, and the remaining 0s in the result will be discarded in the mapping. Since the bandwidth is only L long, corresponding to the number of elements contained in the final column vector, it is equivalent to b nThe n-point FFT transform is shortened to L length through the LS optimization.

[0157] Based on the shiftable extended generation method, the LS optimization mapping of different frequency domain positions is realized by using the phase transformation factor. The approximate expression of the LS optimization corresponding to the shiftable extended generation method is shown in formula (8):

[0158]

[0159] Among them, x LS is the frequency domain signal after LS optimization; F inv is the inverse matrix of Fourier transform; G is the intercept matrix; b n is the extended signal block; w is the phase change sequence of the current bit based on the mapping position, kc is the starting position of frequency domain mapping.

[0160] The starting position of the frequency domain mapping is also the starting RE of the frequency domain mapping, and the starting RE can be any RE on any RB. For example, when kc=0, the starting position of the frequency domain mapping is the 0th RE on the RB, when kc=3, the starting position of the frequency domain mapping is the 3rd RE on the RB, and so on. When kc=0, the calculation result in expression (7) can be obtained according to formula (8), as shown in expression (9):

[0161]

[0162] According to formula (8), by changing kc, the phase can be moved, so the appropriate generation phase can be selected for the Fourier transform matrix to offset the pre-distortion phase, so that the result still becomes the FFT effect based on LS optimization, as shown in expression (10):

[0163]

[0164] For the shiftable extension generation method described above, although a good convergence effect can be obtained, the spectrum energy is too concentrated. When passing through a channel with strong frequency selectivity, once the peak falls into the deep attenuation area, most of the energy will be lost, causing the waveform at the receiving end to be completely distorted. In view of this, after obtaining multiple waveforms to be processed corresponding to an OFDM symbol, formula (8) can be used to perform time-frequency conversion on each waveform to be processed to obtain a frequency domain signal corresponding to each waveform to be processed, and then a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal is obtained based on the frequency domain signal corresponding to each waveform to be processed. The expression of the frequency domain signal corresponding to the waveform to be processed with index i and obtained after LS optimization is shown in formula (11):

[0165]

[0166] in, is the frequency domain signal sequence corresponding to the i-th waveform to be processed, Each element in is a frequency domain signal mapped to different resource elements RE; is the interception matrix constructed according to the frequency domain bandwidth of the LP-WUS signal; F inv is the inverse Fourier transform matrix; F inv The conjugate transposed matrix of ; is the phase change sequence corresponding to the i-th OOK waveform to be processed; is the phase transformation basis; N is the number of sampling points, kc is the index of the starting frequency domain mapping position of the OOK waveform to be processed with index 0, and the starting frequency domain mapping position can be on any RE of any resource block RB.

[0167] By expanding formula (11), the frequency domain signal after LS optimization can be obtained as shown in formula (12):

[0168]

[0169] Among them, the rightmost sequence is the generated frequency domain signal corresponding to each waveform to be processed, and each signal is a signal mapped to a different RE on the same OFDM symbol. Since the frequency domain signals corresponding to all the waveforms to be processed with different phases need to be intercepted and spliced ​​after obtaining them, only part of the frequency domain signal intercepted from the frequency domain signal corresponding to the waveform to be processed is finally mapped to different REs on the same OFDM symbol. From the expression of the analysis signal, it can be seen that each signal has different phase information. For example, the phase information corresponding to the 0th signal is 1, and the phase information corresponding to the 1st signal is The phase information corresponding to the second signal is ..., the phase information corresponding to the R-1th signal is

[0170] Based on formula (12), the frequency domain signal corresponding to the Q waveforms to be processed can be obtained. Specifically:

[0171] The frequency domain signal corresponding to the waveform to be processed with index 0 is:

[0172]

[0173] The frequency domain signal corresponding to the waveform to be processed with index 1 is:

[0174]

[0175] The frequency domain signal corresponding to the waveform to be processed with index Q-1 is:

[0176]

[0177] From the expression of the analysis signal, we can know that each signal has different starting position information. For example, the 0th signal on the OOK waveform to be processed with the 0th index means that the Fourier matrix starts from the kth c Starting from position, it means that in frequency domain mapping, only the frequency domain signal generated on the right is mapped in the frequency domain from item 0 to kc and the corresponding positions thereafter, that is, item 0 in the frequency domain signal is mapped to RE with index kc, and item 1 in the frequency domain signal is mapped to RE with index kc. c +1 RE, and so on, the waveform after OFDM signal modulation is the correct OOK waveform; similarly, the 0th bit signal on the OOK waveform to be processed with the 1st index means that the Fourier matrix is ​​from the kth c +R / Q position, which means that in the frequency domain mapping, only the right side generated signal is mapped from the 0th item to the kth item in the frequency domain. c +R / Q and the corresponding positions thereafter, the waveform after being modulated by the OFDM signal is the correct OOK waveform; similarly, for the 0th bit signal on the OOK waveform to be processed at the i-th index, it means that the Fourier matrix is ​​from the k-th c +iR / Q position, which means that in the frequency domain mapping, only the right side generated signal is mapped from the 0th item to the kth item in the frequency domain. c +iR / Q and the corresponding positions thereafter, the waveform after being modulated by the OFDM signal is the correct OOK waveform.

[0178] (2) Signal-level DFT transform precoding scheme

[0179] The matrix-level LS optimization scheme is a scheme for processing the waveform to be processed corresponding to the OFDM symbol. Considering that the essence of processing the waveform to be processed corresponding to the OFDM symbol is to process each signal in the waveform to be processed, in order to clearly understand the technical scheme of the present invention, the method of performing signal-level processing on the waveform to be processed with different phases in an embodiment of the present invention to obtain the corresponding frequency domain signal is explained below.

[0180] In an exemplary embodiment of the present disclosure, the corresponding frequency domain signal can be obtained by performing DFT transform precoding or LS optimization on the signal in the waveform to be processed with different phases. When performing DFT transform precoding, the number of sampling points of DFT transform precoding is the same as the bandwidth, that is, the number of time domain points is the same as the number of frequency domain points. Specifically, DFT transform precoding can be performed according to formula (13):

[0181]

[0182] Where y(·) is the frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; The number of sampling points corresponding to DFT transform precoding; is the phase-shifted signal block corresponding to the lth OFDM symbol.

[0183] In an exemplary embodiment of the present disclosure, according to formula (14), only one set (l, k) needs to be determined each time to obtain the frequency domain signal generated by DFT transform precoding corresponding to the kth RE in the OFDM symbol with index l. For example, l=1, k=k c +R / Q, according to formula (13), the kth OFDM symbol mapped to index 1 can be calculated c The expression of the frequency domain signal on the +R / Q position RE is:

[0184] It is worth noting that the coefficients in formula (13) The function of is to correct the deviation in the frequency domain signal generation process to ensure that the generated frequency domain signal is closer to the real signal.

[0185] (3) Signal-level LS optimization solution

[0186] In an exemplary embodiment of the present disclosure, when the LS optimization scheme is used to perform time-frequency conversion of a signal, the number of sampling points is greater than or equal to the bandwidth size, that is, the number of frequency domain points can be equal to the number of time domain points, or can be greater than the number of time domain points. In an embodiment of the present disclosure, LS optimization can be performed according to formula (14), as follows:

[0187]

[0188] Where y(·) is the frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; Optimize the number of sampling points corresponding to LS; is the bandwidth of the LP-WUS signal in the frequency domain; β is the power control factor; is the phase-shifted signal block corresponding to the lth OFDM symbol.

[0189] In an exemplary embodiment of the present disclosure, similar to the DFT transform precoding scheme, according to formula (11), only a unique set of (l, k) needs to be determined each time to obtain the frequency domain signal generated by LS optimization corresponding to the kth RE in the OFDM symbol with index l, and the frequency domain signal corresponds to the frequency domain signal in the frequency domain signal sequence shown in formula (9). For example, take l=1, k=k c +R / O, according to formula (14), the kth OFDM symbol mapped to index 1 can be calculated c The expression of the frequency domain signal on the +R / Q position RE is:

[0190] It is worth noting that the power control factor β in formula (14) is used to ensure that the average value of the signal-noise ratio (Signal-Noise Ratio, SNR or S / N) is the same as the signal-noise ratio in the physical downlink shared channel (Physical Downlink Shared Channel, PDSCH), and further, it can also be used to ensure that the average value of the signal-to-interference ratio (Signal to Interference Ratio, SIR) is the same as the signal-to-interference ratio in the PDSCH, and the average value of the signal-to-interference and noise ratio (Signal to Interference and noise Ratio, SINR) is the same as the signal-to-interference and noise ratio in the PDSCH.

[0191] In the above embodiments, the matrix-level LS optimization scheme, the signal-level DFT transform precoding scheme, and the signal-level LS optimization scheme are described. The purpose of these optimization schemes is the same, which is to convert the time domain signal corresponding to the waveform to be processed into a frequency domain signal. Since the number of time domain points in the LS optimization scheme can be greater than the number of frequency domain bandwidth points, and the more time domain points, the better the approximation effect, the LS optimization scheme can better approximate the original OOK waveform to be approximated and has better performance than the DFT transform precoding scheme for signal processing.

[0192] In an exemplary embodiment of the present disclosure, in step S260, DFT transform precoding or LS optimization is performed on the waveforms to be processed with different phases. After the frequency domain signals corresponding to each waveform to be processed are obtained, all frequency domain signals corresponding to an OFDM symbol can be intercepted and spliced ​​to obtain a target frequency domain signal corresponding to the OFDM symbol and having the same size as the frequency domain bandwidth of the LP-WUS signal. The target frequency domain signal is the frequency domain signal mapped to the OFDM modulator. When intercepting the frequency domain signal, since the first half of the frequency domain signal is the part where the frequency domain energy is concentrated, the frequency domain energy of the second half is very low, the contribution to the whole is very small, and it is also easy to cause very low spectral efficiency. Therefore, when intercepting the frequency domain signal, the head of the frequency domain signal can be intercepted, and then splicing is performed according to the intercepted target frequency domain signal segment to obtain a target frequency domain signal having the same size as the frequency domain bandwidth of the LP-WUS signal.

[0193] In an exemplary embodiment of the present disclosure, the frequency domain signals corresponding to each waveform to be processed can be intercepted with target frequency domain signal segments of equal or unequal lengths, on the premise that the size of the target frequency domain signal finally spliced ​​is the same as the frequency domain bandwidth size of the LP-WUS signal. If the approximated OOK waveform is repeated to form Q OOK waveforms to be processed, when intercepting target frequency domain signal segments of equal lengths, the frequency domain signal of the head 1 / Q part of each waveform to be processed can be intercepted to form a target frequency domain signal segment; when intercepting target frequency domain signal segments of unequal lengths, the head of each waveform to be processed can be intercepted with different lengths according to a preset rule, wherein the preset rule can be that the lengths of the target frequency domain signal segments corresponding to multiple adjacent waveforms to be processed are equal, for example, the lengths of the target frequency domain signal segments corresponding to two adjacent waveforms to be processed are equal, and so on. Of course, it can also be other rules, as long as the size of the target frequency domain signal is ensured to be the same as the size of the frequency domain signal of the LP-WUS signal, and the embodiment of the present disclosure does not make specific limitations on this.

[0194] In an exemplary embodiment of the present disclosure, similar to performing phase transformation on the OOK waveform to be processed and performing DFT transform precoding or LS optimization on the waveform to be processed with a different phase obtained by the phase transformation, performing head interception on each waveform to be processed to obtain the target frequency domain signal segment can also be divided into matrix-level operations and signal-level operations. Similarly, since matrix-level DFT transform precoding is a commonly used signal transformation method in this field, this is not explained in detail in the embodiments of the present disclosure. Next, only the matrix-level interception scheme corresponding to the matrix-level LS optimization scheme, the signal-level interception scheme corresponding to the signal-level DFT transform precoding, and the signal-level interception scheme corresponding to the signal-level LS optimization scheme are described in detail. It is worth noting that in the embodiments of the present disclosure, only the scheme of how to perform equal-length interception on the frequency domain signal of the waveform to be processed is described.

[0195] (1) Matrix-level truncation scheme corresponding to the matrix-level LS optimization scheme

[0196] When the frequency domain signal of the head 1 / Q part of each waveform to be processed is intercepted to form the target frequency domain signal segment, the first 1 / Q part of each frequency domain signal is intercepted to obtain the intercepted frequency domain signal segment, and then the power control factor β and the power coefficient are used to calculate the target frequency domain signal segment. The intercepted frequency domain signal segment is processed to obtain the target frequency domain signal segment. Among them, the power control factor β is the same as β in formula (14), which will not be repeated here. The power coefficient It is used to ensure that the power of the target frequency domain signal corresponding to each frequency domain signal segment is equal to the power of the OOK waveform to be approximated.

[0197] Taking formula (12) as an example, the intercepted frequency domain signal segment obtained by interception based on formula (12) and the index of the waveform to be processed, the frequency domain signal corresponding to the waveform to be processed, and the number of waveforms to be processed satisfy the relationship (15):

[0198]

[0199] Next, according to the power control factor β and power coefficient The intercepted frequency domain signal segment shown in formula (16) is processed to obtain a target frequency domain signal segment, and the target frequency domain signal segment and the intercepted frequency domain signal segment satisfy the relationship (16):

[0200]

[0201] in, is the target frequency domain signal segment; X i is the frequency domain signal segment to be intercepted; i is the index of the waveform to be processed; Q is the number of waveforms to be processed; R is the frequency domain bandwidth of LP-WUS; β is the power control factor; is the phase transformation basis, N is the number of sampling points; kc is the index of the starting frequency domain mapping position corresponding to the i-th waveform to be processed.

[0202] (2) Signal-level interception scheme corresponding to signal-level DFT transform precoding

[0203] Based on the DFT transform precoding of the processed waveform as shown in formula (13), the corresponding frequency domain signal is obtained, and the first 1 / Q part of the target frequency domain signal segment can be intercepted for the frequency domain signal. When the first 1 / Q part of the target frequency domain signal segment is intercepted for each frequency domain signal, the index k of the RE position can be limited according to 1 / Q to ensure that the target frequency domain signal segment with a length of 1 / Q of the total length of the frequency domain signal is obtained through DFT transform precoding. Specifically, the target frequency domain signal segment and the index of the OFDM symbol, the RE position index on the OFDM symbol, and the number of sampling points corresponding to the DFT transform precoding satisfy the relationship (17):

[0204]

[0205] Where y(·) is the frequency domain signal in the target frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; The number of sampling points corresponding to DFT transform precoding; is the phase transformation signal block corresponding to the OFDM symbol indexed as l; Q is the total number of frequency domain signals generated by DFT transform precoding; m is the index of the frequency domain signal corresponding to the OFDM symbol indexed as l.

[0206] By comparing formula (13) and formula (17), it can be seen that the only difference between the two is that formula (17) uses m and Q to limit the value of k. In this way, formula (17) can be used to ensure that the target frequency domain signal segment of the first 1 / Q part of different frequency domain signals is obtained, that is, the head of the full-bandwidth frequency domain signal obtained according to formula (13) is intercepted.

[0207] (3) Signal-level interception scheme corresponding to signal-level LS optimization

[0208] Based on the LS optimization of the processed waveform shown in formula (14), the corresponding frequency domain signal is obtained, and the first 1 / Q part of the target frequency domain signal segment can be intercepted for the frequency domain signal. When the first 1 / Q part of the target frequency domain signal segment is intercepted for each frequency domain signal, the index k of the RE position can be limited according to 1 / Q to ensure that the target frequency domain signal segment with a length of 1 / Q of the total length of the frequency domain signal is obtained through LS optimization. Specifically, the index of the target frequency domain signal segment and the OFDM symbol, the RE position index on the OFDM symbol, the frequency domain bandwidth size of the LP-WUS signal, and the number of sampling points corresponding to the LS optimization satisfy the relationship (18):

[0209]

[0210] Where y(·) is the frequency domain signal in the target frequency domain signal segment; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; Optimize the number of sampling points corresponding to LS; is the frequency domain bandwidth of the LP-WUS signal; β is the power control factor; is the phase transformation signal block corresponding to the first OFDM symbol; Q is the total number of frequency domain signals generated by LS optimization; m is the index of the frequency domain signal corresponding to the OFDM symbol with index 1.

[0211] By comparing formula (14) and formula (18), it can be seen that the only difference between the two is that formula (18) uses m and Q to limit the value of k. In this way, formula (18) can be used to ensure that the target frequency domain signal segment of the first 1 / Q part of different frequency domain signals is obtained, that is, the head of the full-bandwidth frequency domain signal obtained according to formula (14) is intercepted.

[0212] In an exemplary embodiment of the present disclosure, after completing the interception of the frequency domain signals of the waveforms to be processed with different phases, all the acquired target frequency domain signal segments can be sorted according to the starting frequency domain mapping positions corresponding to each waveform to be processed, and then spliced ​​to obtain the target frequency domain signal.

[0213] Figures 14A-14D The schematic diagram of the interface for performing equal-length interception of waveforms to be processed with different phases corresponding to an OFDM symbol is shown schematically, such as Fig.14A As shown, there are Q waveforms to be processed, each of which corresponds to a different starting frequency domain mapping position, and the starting frequency domain mapping position corresponding to the 0th waveform to be processed is k c , the starting frequency domain mapping position corresponding to the first waveform to be processed is The starting frequency domain mapping position corresponding to the i-th waveform to be processed is The starting frequency domain mapping position corresponding to the Q-1th waveform to be processed is After performing DFT transform precoding or LS optimization on the Q waveforms to be processed according to the frequency domain bandwidth of the LP-WUS signal, Q frequency domain signals can be generated, and each frequency domain signal corresponds to a different starting frequency domain mapping position, such as Fig. 14B As shown; then the first 1 / Q part of each frequency domain signal can be intercepted to obtain the target frequency domain signal segment, such as Fig. 14CAs shown; finally, the Q target frequency domain signal segments are spliced ​​according to the corresponding starting frequency domain mapping positions to obtain a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal, as shown Fig.14D shown.

[0214] In an exemplary embodiment of the present disclosure, after acquiring the target frequency domain signal, a target transmission signal may be generated based on the target frequency domain signal, where the target transmission signal is a signal including an LP-WUS signal and is sent to the UE.

[0215] Among them, when generating a target transmission signal based on a target frequency domain signal, a frequency domain signal corresponding to RE on each OFDM symbol generated by a DFT transform precoding scheme or a LS optimization scheme can be input into an OFDM modulator, mapped to RE in the OFDM modulator, and then OFDM modulated by the OFDM modulator to obtain a target OOK waveform that approximates the OOK waveform to be approximated. Further, a target transmission signal can be constructed according to the target OOK waveform. Figure 3 Taking the OFDM baseband signal processing principle diagram shown as an example, after all signal blocks corresponding to the LP-WUS signal are processed according to the above embodiment to generate corresponding frequency domain signals, the frequency domain signals can be mapped to different REs in the OFDM modulator, and then the frequency domain signals corresponding to different signal blocks are subjected to frequency domain-time domain conversion processing. For example, the inverse fast Fourier transform method (IFFT) can be used to perform frequency domain-time domain conversion processing to obtain a time domain signal corresponding to the input frequency domain signal. Then, the time domain signals corresponding to different signal blocks can be subjected to parallel-to-serial conversion, and the time domain signals corresponding to different signal blocks can be spliced ​​in sequence to obtain the target OOK waveform. Finally, in order to ensure the security of signal transmission, a protection interval can be added to the target OOK waveform, such as padding zeros in the protection interval or adding a cyclic prefix to avoid inter-symbol interference, and the target transmitted signal can be obtained.

[0216] In an exemplary embodiment of the present disclosure, after acquiring the target transmission signal, the target transmission signal can be sent to the UE end through a multipath fading channel. After the wake-up signal receiver in the UE end receives the target transmission signal, the target transmission signal can be envelope detected to obtain the LP-WUS signal. The processing flow of the wake-up signal receiver on the target transmission signal is the same as that of the Figure 3 The receiving end processing flow is the same as that shown in , and the embodiments of the present disclosure will not be repeated here.

[0217] The signal generation method in the disclosed embodiment performs phase transformation on multiple OOK waveforms to be processed corresponding to the OOK waveform to be approximated according to different phase rotation sequences to obtain multiple waveforms to be processed with different phases, then performs DFT transformation precoding or LS optimization on the waveforms to be processed with different phases to obtain corresponding frequency domain signals, and finally intercepts and splices the frequency domain signals to obtain a target frequency domain signal with the same frequency domain bandwidth as the LP-WUS signal. Since only the head of the frequency domain signal with concentrated energy is intercepted during interception, the target frequency domain signal obtained by splicing the intercepted frequency domain signal segment expands the bandwidth of the main energy part of the LP-WUS signal, thereby improving the frequency diversity gain of the LP-WUS signal, so that when the target transmitted signal passes through a multipath fading channel or a channel with strong frequency selectivity, as long as not all bandwidths are located at the deep attenuation point of the channel, at least one frequency domain peak will not be affected, and has an envelope that can be distinguished from noise, ensuring that after the UE receives the LP-WUS signal, the LP-WUS signal can be detected by the envelope detection method, thereby improving the detection rate and detection accuracy of the LP-WUS signal.

[0218] Furthermore, the wake-up signal receiver can wake up the main wireless module MR in the UE according to the demodulated LP-WUS signal, ensure the signal synchronization between MR and the base station, realize the basic functions of the UE, and achieve the purpose of saving energy consumption.

[0219] Furthermore, although the steps of the method in the present disclosure are described in a particular order in the drawings, this does not require or imply that the steps must be performed in this particular order or that all the steps shown must be performed to achieve the desired results.

[0220] In some embodiments, certain steps may be omitted, multiple steps may be combined into one step, and / or one step may be decomposed into multiple steps.

[0221] Based on the same inventive concept, the present disclosure also provides a signal generating device in the following embodiments. Since the principle of solving the problem in the device embodiment is similar to that in the above method embodiment, the implementation of the device embodiment can refer to the implementation of the above method embodiment, and the repeated parts will not be repeated.

[0222] Figure 1 5 shows a schematic diagram of a signal generating device in an embodiment of the present disclosure, such as Figure 1 As shown in FIG. 5 , the signal generating device 1500 includes:

[0223] The waveform processing module 1502 is used to break up the OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal to obtain a waveform to be processed with different phases;

[0224] An optimization module 1504 is used to perform DFT transformation precoding or least squares LS optimization on the waveform to be processed to obtain a frequency domain signal corresponding to the waveform to be processed;

[0225] The frequency domain processing module 1506 is configured to obtain a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal.

[0226] In some embodiments, the waveform processing module 1 502 is used to generate an OOK waveform to be approximated based on the LP-WUS signal; use a sequence with the same modulus value but different phase to break up the OOK waveform to be approximated to obtain an OOK waveform to be approximated with the same modulus value but different phase; repeat the OOK waveform to be approximated with the same modulus value but different phase according to a preset number to generate multiple OOK waveforms to be processed; perform phase transformation on each OOK waveform to be processed according to different frequency domain mapping positions to obtain multiple waveforms to be processed with different phases.

[0227] In some embodiments, an OOK waveform to be approximated is generated based on the LP-WUS signal, including: rate matching the number of bits contained in the LP-WUS signal according to the number of bits that can be carried by an orthogonal frequency division multiplexing OFDM symbol to divide the LP-WUS signal into multiple signal blocks; time domain expansion and OOK modulation are performed on each signal block to obtain an OOK waveform to be approximated corresponding to each signal block.

[0228] In some embodiments, performing time domain spreading and OOK modulation on each signal block includes:

[0229] The signal block is time-domain extended according to the number of sampling points corresponding to the DFT transform precoding or LS optimization, and the extended signal block obtained by the time-domain extension is OOK modulated to obtain the OOK waveform to be approximated.

[0230] In some embodiments, the signal blocks are time-domain expanded according to the sampling points corresponding to the DFT transform precoding or LS optimization, including: when the processed waveform is subjected to DFT transform precoding, the signal blocks corresponding to each OFDM symbol are time-domain expanded according to the sampling points corresponding to the LP-WUS signal bandwidth size, and the portion of the OFDM symbol not covered by the extended signal is filled with zeros; when the processed waveform is subjected to LS optimization, the signal blocks corresponding to each OFDM symbol are time-domain expanded according to the sampling points corresponding to the LS optimization, and the portion of the OFDM symbol not covered by the extended signal is filled with zeros.

[0231] In some embodiments, a sequence with the same modulus value but different phase is used to break up the OOK waveform to be approximated to obtain an OOK waveform with the same modulus value but different phase, including: using a sequence including multiple phase rotation factors with the same modulus value and phases changing according to a preset change rule to perform phase rotation on the OOK waveform to be approximated to obtain an OOK waveform with the same modulus value but different phase; or, using a constant modulus sequence to replace the high-level ON waveform of the OOK waveform to be approximated to obtain an OOK waveform with the same modulus value but different phase, and the constant modulus sequence is a group of sequences with the same modulus value but different phases.

[0232] In some embodiments, a sequence of phase rotation factors having the same modulus and phases changing according to a preset change rule is used to perform phase rotation on the OOK waveform to be approximated, so as to obtain an OOK waveform to be approximated with the same modulus but a different phase, wherein the preset change rule includes: the phase changes at a preset interval, or the phase is partially repeated and the phase of the non-repeating part changes at a preset interval.

[0233] In some embodiments, before using a sequence of phase rotation factors having the same modulus and whose phases change according to a preset change rule to perform phase rotation on the approximated OOK waveform, it also includes: constructing a sequence according to the phase rotation factors generated according to the preset change rule.

[0234] In some embodiments, when the preset variation rule is that the phase changes at a preset interval, a sequence is constructed according to the phase rotation factor generated according to the preset variation rule, including: determining a variation sequence according to a preset number of sampling points, a preset interval, and a parameter corresponding to an OFDM symbol, performing a modulo remainder operation on the variation sequence and the phase rotation parameter to obtain a phase rotation coefficient sequence; A phase rotation basis is a phase rotation basis, a plurality of phase rotation factors are generated according to the phase rotation basis and a phase rotation coefficient sequence, and a sequence is constructed according to the phase rotation factors.

[0235] In some embodiments, when the preset variation rule is that the phase part is repeated and the phase of the non-repeating part changes at a preset interval, a sequence is constructed according to the phase rotation factor generated according to the preset variation rule, including: determining a variation sequence according to a preset number of sampling points, a preset interval and a parameter corresponding to an OFDM symbol, performing a modulo remainder operation on the variation sequence and the phase rotation parameter to obtain a phase rotation coefficient sequence; A phase rotation base is used, multiple phase rotation factors are generated according to the phase rotation base and the phase rotation coefficient sequence, and an initial sequence is constructed according to the phase rotation factors; the phase rotation factors to be repeated in the initial sequence are repeated according to a preset repetition amount to obtain a sequence.

[0236] In some embodiments, generating a plurality of phase rotation factors according to a phase rotation basis and a phase rotation coefficient sequence, and constructing an initial sequence according to the phase rotation factors comprises:

[0237] The sequence, phase rotation basis, and phase rotation coefficient sequence satisfy the relationship (1):

[0238]

[0239] Among them, α i (m i ) is a sequence; l is the index of the OFDM symbol; m i +r is the sequence of variation; i is the index of variation, which is a non-negative integer; N is the number of preset sampling points, which is an arbitrary positive integer; r is the parameter corresponding to the OFDM symbol, which is a non-negative integer; μ is the phase rotation parameter, which is an arbitrary positive number; p is the preset interval; m i modμ is the phase rotation coefficient sequence.

[0240] In some embodiments, it also includes: when the indexes of OFDM symbols are different, the r corresponding to each OFDM symbol is 0; when the indexes of OFDM symbols are different, the r corresponding to each OFDM symbol is the index of the OFDM symbol; or, when the indexes of OFDM symbols are different, the r corresponding to each OFDM symbol is an arbitrary value that is different from each other.

[0241] In some embodiments, the preset number of sampling points is the number of sampling points of the ON waveform corresponding to the OOK waveform to be approximated or the number of sampling points in the OOK waveform to be approximated; and further includes:

[0242] When the preset sampling points are the sampling points corresponding to the ON waveform,

[0243] When the preset number of sampling points is the number of sampling points in the OOK waveform to be approximated,

[0244] in, is the number of bits contained in the extended signal block corresponding to the OFDM symbol, It is the number of bits carried by one OFDM symbol during rate matching.

[0245] In some embodiments, a sequence of phase rotation factors having the same modulus and phases changing according to a preset change rule is used to perform phase rotation on the OOK waveform to be approximated, including:

[0246] The waveform to be processed is obtained by multiplying the sequence of phase rotation factors with the OOK waveform to be approximated, or by multiplying the sequence of phase rotation factors with the high-level ON waveform of the OOK waveform to be approximated.

[0247] In some embodiments, the constant modulus sequence includes one or more of the following sequences:

[0248] ZC sequence, random orthogonal amplitude modulation sequence, CGS sequence, low PAPR sequence.

[0249] In some embodiments, a constant modulus sequence is used to replace a high-level ON waveform of an OOK waveform to be approximated, so as to obtain an OOK waveform to be approximated with the same modulus value but different phase, including:

[0250] Based on the preset substitution rule, the high-level ON waveform of the OOK waveform to be approximated is replaced by a constant modulus sequence to obtain an OOK waveform to be approximated with the same modulus value but different phase, wherein the preset substitution rule includes:

[0251] The constant modulus sequence corresponding to each ON waveform is the same, the constant modulus sequence corresponding to each ON waveform is different, and the constant modulus sequences corresponding to some ON waveforms among the multiple ON waveforms are the same.

[0252] In some embodiments, the preset number is smaller than the frequency domain bandwidth of the LP-WUS signal and is an integer multiple of the frequency domain bandwidth of the LP-WUS signal.

[0253] In some embodiments, phase transformation is performed on a plurality of OOK waveforms to be processed according to different frequency domain mapping positions to obtain a plurality of waveforms to be processed with different phases, including:

[0254] Determine a starting frequency domain mapping position corresponding to each OOK waveform to be processed, and determine a phase transformation sequence corresponding to the OOK waveform to be processed according to the starting frequency domain mapping position;

[0255] Performing phase transformation on the corresponding OOK waveform to be processed according to the phase transformation sequence to obtain the waveform to be processed;

[0256] The starting frequency domain mapping position is any RE in the OFDM symbol, and the phase transformation factors in the phase transformation sequence are continuous.

[0257] In some embodiments, determining a starting frequency domain mapping position corresponding to each OOK waveform to be processed, and determining a phase transformation sequence corresponding to the OOK waveform to be processed according to the starting frequency domain mapping position includes:

[0258] Determine the starting frequency domain mapping position corresponding to each OOK waveform to be processed according to the starting frequency domain mapping position corresponding to the OOK waveform to be processed with index 0, the index corresponding to each OOK waveform to be processed, the preset number and the frequency domain bandwidth size of the LP-WUS signal;

[0259] According to the phase transformation The starting frequency domain mapping position corresponding to the OOK waveform to be processed and the position index of each bit in the OOK waveform to be processed determine the phase transformation factor corresponding to each bit in the OOK waveform to be processed;

[0260] A phase shift sequence is constructed according to all phase shift factors corresponding to the OOK waveform to be processed.

[0261] In some embodiments, performing phase transformation on the corresponding OOK waveform to be processed according to the phase transformation sequence to obtain the waveform to be processed includes:

[0262] The waveform to be processed, the phase change sequence, and the OOK waveform to be processed satisfy the following relationship:

[0263]

[0264] in, is the matrix representation of the waveform to be processed; is the phase change sequence corresponding to the i-th OOK waveform to be processed; is the matrix representation of the i-th OOK waveform to be processed; i is the index of the OOK waveform to be processed; R is the frequency domain bandwidth of the LP-WUS signal; Q is the number of OOK waveforms to be processed, which is a positive integer greater than 1; kc is the index of the starting frequency domain mapping position of the OOK waveform to be processed with index 0; is the phase transformation basis; N is the total number of bits contained in the OOK waveform to be processed.

[0265] In some embodiments, performing phase transformation on the corresponding OOK waveform to be processed according to the phase transformation sequence to obtain the waveform to be processed includes:

[0266] The waveform to be processed, the phase change sequence, and the OOK waveform to be processed satisfy the following relationship:

[0267]

[0268] in, is the signal in the waveform to be processed; is the signal in the OOK waveform to be processed; is the phase change sequence corresponding to the OFDM symbol with index l; i' is the position index corresponding to each signal on the OFDM symbol; is the number of bits contained in the extended signal block corresponding to an OFDM symbol; kc is the index of the starting frequency domain mapping position of the OOK waveform to be approximated with index 0.

[0269] In some embodiments, performing least squares LS optimization on waveforms to be processed with different phases to obtain frequency domain signals corresponding to each waveform to be processed includes:

[0270] LS optimization is performed on the waveform to be processed according to the interception matrix, the inverse Fourier transform matrix, and the phase transformation sequence, wherein the frequency domain signal satisfies the relationship between the waveform to be processed, the interception matrix, the inverse Fourier transform matrix, and the phase transformation sequence:

[0271]

[0272] in, is the frequency domain signal sequence corresponding to the i-th waveform to be processed, Each element in is a frequency domain signal mapped to different resource elements RE; is the truncation matrix constructed according to the frequency domain bandwidth of the LP-WUS signal; F inv is the inverse Fourier transform matrix; F inv The conjugate transposed matrix of ; is the phase change sequence corresponding to the i-th OOK waveform to be processed;

[0273] is the phase transformation basis; N is the number of sampling points, k c is the index of the starting frequency domain mapping position of the OOK waveform to be processed with index 0. The starting frequency domain mapping position can be on any RE of any resource block RB.

[0274] In some embodiments, performing DFT transformation precoding on waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed includes:

[0275] The frequency domain signal and the index of the OFDM symbol, the RE position index on the OFDM symbol, and the number of sampling points corresponding to the DFT transform precoding satisfy the relationship:

[0276]

[0277] Where y(·) is the frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; The number of sampling points corresponding to DFT transform precoding; is the phase-shifted signal block corresponding to the lth OFDM symbol.

[0278] In some embodiments, performing least squares LS optimization on waveforms to be processed with different phases to obtain frequency domain signals corresponding to each waveform to be processed includes:

[0279] The frequency domain signal and the index of the OFDM symbol, the RE position index on the OFDM symbol, the frequency domain bandwidth size of the LP-WUS signal, and the number of sampling points corresponding to the LS optimization satisfy the relationship:

[0280]

[0281] Where y(·) is the frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; Optimize the number of sampling points corresponding to LS; is the frequency domain bandwidth of the LP-WUS signal; β is the power control factor; is the phase-shifted signal block corresponding to the first OFDM symbol.

[0282] In some embodiments, the number of frequency domain signals is multiple;

[0283] Acquiring a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal, including:

[0284] The header of each frequency domain signal is intercepted to obtain a target frequency domain signal segment corresponding to each frequency domain signal;

[0285] All target frequency domain signal segments are sequentially concatenated to obtain the target frequency domain signal.

[0286] In some embodiments, intercepting the header of each frequency domain signal to obtain a target frequency domain signal segment corresponding to each frequency domain signal includes:

[0287] intercepting the first 1 / Q part of each frequency domain signal to obtain an intercepted frequency domain signal segment;

[0288] According to the power control factor β and power coefficient Processing the intercepted frequency domain signal segment to obtain a target frequency domain signal segment;

[0289] Among them, Q is the number of OOK waveforms to be processed; the power control factor is used to ensure that the average value of the signal-to-noise ratio is the same as the signal-to-noise ratio in the physical downlink shared channel PDSCH; the power coefficient is used to ensure that the power of the target frequency domain signal corresponding to each frequency domain signal segment is equal to the power of the OOK waveform to be approximated.

[0290] In some embodiments, intercepting the first 1 / Q part of each frequency domain signal to obtain an intercepted frequency domain signal segment includes:

[0291] The intercepted frequency domain signal segment and the index of the waveform to be processed, the frequency domain signal corresponding to the waveform to be processed, and the number of waveforms to be processed satisfy the relationship:

[0292]

[0293] According to the power control factor β and power coefficient The intercepted frequency domain signal segment is processed to obtain the target frequency domain signal segment, including:

[0294] The target frequency domain signal segment and the intercepted frequency domain signal segment satisfy the relationship:

[0295]

[0296] in, is the target frequency domain signal segment; X i is the frequency domain signal segment to be intercepted; i is the index of the waveform to be processed; Q is the number of waveforms to be processed; R is the frequency domain bandwidth of LP-WUS; β is the power control factor; is the phase transformation basis, N is the number of sampling points; kc is the index of the starting frequency domain mapping position corresponding to the 0th waveform to be processed.

[0297] In some embodiments, intercepting the header of each frequency domain signal to obtain a target frequency domain signal segment corresponding to each frequency domain signal includes:

[0298] The target frequency domain signal segment and the index of the OFDM symbol, the RE position index on the OFDM symbol, and the number of sampling points corresponding to the DFT transform precoding satisfy the relationship:

[0299]

[0300] Where y(·) is the frequency domain signal in the target frequency domain signal segment; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; The number of sampling points corresponding to DFT transform precoding; is the phase transformation signal block corresponding to the OFDM symbol with index 1; Q is the total number of frequency domain signals generated by DFT transform precoding; m is the index of the frequency domain signal corresponding to the OFDM symbol with index l.

[0301] In some embodiments, intercepting the header of each frequency domain signal to obtain a target frequency domain signal segment corresponding to each frequency domain signal includes:

[0302] The target frequency domain signal segment and the index of the OFDM symbol, the RE position index on the OFDM symbol, the frequency domain bandwidth size of the LP-WUS signal, and the number of sampling points corresponding to the LS optimization satisfy the relationship:

[0303]

[0304] Where y(·) is the frequency domain signal in the target frequency domain signal segment; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from Incremental in sequence; i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; Optimize the number of sampling points corresponding to LS; is the frequency domain bandwidth of the LP-WUS signal; β is the power control factor; is the phase transformation signal block corresponding to the first OFDM symbol; Q is the total number of frequency domain signals generated by LS optimization; m is the index of the frequency domain signal corresponding to the OFDM symbol with index 1.

[0305] In some embodiments, all target frequency domain signal segments are sequentially spliced ​​to obtain a target frequency domain signal, including:

[0306] All target frequency domain signal segments are sorted and spliced ​​according to the starting frequency domain mapping positions corresponding to the target frequency domain signal segments to obtain the target frequency domain signal.

[0307] In some embodiments, it also includes: generating a target transmission signal based on the frequency domain signal.

[0308] In some embodiments, a target transmission signal is generated based on a frequency domain signal, including: mapping the frequency domain signal corresponding to the RE on each OFDM symbol to the RE in the OFDM modulator; performing OFDM modulation on the frequency domain signal through the OFDM modulator to obtain a target OOK waveform that approximates the OOK waveform to be approximated, and constructing a target transmission signal based on the target OOK waveform.

[0309] In some embodiments, it also includes: sending the target transmission signal to a wake-up signal receiver in the user terminal UE through a multipath fading channel, performing envelope detection on the target transmission signal through the wake-up signal receiver to obtain an LP-WUS signal, and waking up the main wireless module based on the LP-WUS signal.

[0310] The concepts of “first”, “second”, etc. mentioned in the present disclosure are only used to distinguish different devices, modules or units, and are not used to limit the order or interdependence of the functions performed by these devices, modules or units.

[0311] Regarding the signal generating device in the above embodiment, the specific manner in which each module performs operations has been described in detail in the embodiment of the signal generating method, and will not be elaborated here.

[0312] It should be noted that, although several modules or units of the device for action execution are mentioned in the above detailed description, such division is not mandatory.

[0313] In fact, according to the embodiments of the present disclosure, the features and functions of two or more modules or units described above can be embodied in one module or unit. Conversely, the features and functions of one module or unit described above can be further divided into multiple modules or units to be embodied.

[0314] Some of the blocks shown in the accompanying drawings are functional entities that do not necessarily correspond to physically or logically independent entities. These functional entities can be implemented in software form, or in one or more hardware modules or integrated circuits, or in different networks and / or processor devices and / or microcontroller devices.

[0315] Refer to the following Fig.16 To describe the electronic device provided by the embodiment of the present disclosure. Fig.16 The electronic device 1600 shown is only an example and should not bring any limitation to the functions and scope of use of the embodiments of the present disclosure.

[0316] Fig.16 FIG. 1 is a schematic diagram showing the architecture of an electronic device 1600 provided by an embodiment of the present invention. Fig.16 As shown, the electronic device 1600 includes but is not limited to: at least one processor 1610 and at least one memory 1620.

[0317] The memory 1620 is used to store instructions.

[0318] In some embodiments, the memory 1620 may include a readable medium in the form of a volatile storage unit, such as a random access memory unit (RAM) 16201 and / or a cache memory unit 16202 , and may further include a read-only memory unit (ROM) 16203 .

[0319] In some embodiments, memory 1620 may also include a program / utility 16204 having a set (at least one) of program modules 16205, such program modules 16205 including but not limited to: an operating system, one or more application programs, other program modules, and program data, each of which or some combination may include an implementation of a network environment.

[0320] In some embodiments, the memory 1620 may store an operating system, which may be a real-time operating system (RTX), LINUX, UNIX, WINDOWS, or OS X.

[0321] In some embodiments, data may also be stored in the memory 1620 .

[0322] As an example, the processor 1610 may read data stored in the memory 1620 , where the data may be stored at the same storage address as the instruction, or the data may be stored at a different storage address than the instruction.

[0323] The processor 1610 is used to call the instructions stored in the memory 1620 to implement the steps of various exemplary embodiments of the present disclosure described in the above “Exemplary Method” section of this specification. For example, the processor 1610 can execute each step of the above method embodiment.

[0324] It should be noted that the processor 1610 may be a general-purpose processor or a special-purpose processor. The processor 1610 may include one or more processing cores, and the processor 1610 executes various functional applications and data processing by running instructions.

[0325] In some embodiments, processor 1610 may include a central processing unit (CPU) and / or a baseband processor.

[0326] In some embodiments, the processor 1610 may determine an instruction according to the priority identification and / or function category information carried in each control instruction.

[0327] In the present disclosure, the processor 1610 and the memory 1620 may be provided separately or integrated together.

[0328] As an example, the processor 1610 and the memory 1620 may be integrated on a single board or a system on chip (SOC).

[0329] like Fig.16As shown, the electronic device 1600 is in the form of a general-purpose computing device. The electronic device 1600 may further include a bus 1630 .

[0330] Bus 1630 may be a bus representing one or more of several types of bus structures, including a memory bus or memory controller, a peripheral bus, an accelerated graphics port, a processor, or a local bus using any of a variety of bus architectures.

[0331] The electronic device 1600 may also communicate with one or more external devices 1640 (e.g., keyboards, pointing devices, Bluetooth devices, etc.), one or more devices that enable a user to interact with the electronic device 1600, and / or any device that enables the electronic device 1600 to communicate with one or more other computing devices (e.g., routers, modems, etc.). Such communication may be performed via an input / output (I / O) interface 1650.

[0332] Furthermore, the electronic device 1600 can also communicate with one or more networks (eg, a local area network (LAN), a wide area network (WAN) and / or a public network, such as the Internet) through the network adapter 1660 .

[0333] like Fig.16 As shown, the network adapter 1660 communicates with other modules of the electronic device 1600 via the bus 1630 .

[0334] It should be understood that although not shown in the figures, other hardware and / or software modules may be used in conjunction with the electronic device 1600, including but not limited to: microcode, device drivers, redundant processing units, external disk drive arrays, RAID systems, tape drives, and data backup storage systems.

[0335] It is to be understood that the structure shown in the embodiment of the present disclosure does not constitute a specific limitation on the electronic device 1600. In other embodiments of the present disclosure, the electronic device 1600 may include: Fig.16 More or fewer components may be shown, or some components may be combined or separated, or the components may be arranged differently. Fig.16 The components shown may be implemented in hardware, software or a combination of software and hardware.

[0336] The present disclosure also provides a computer-readable storage medium on which computer instructions are stored. When the computer instructions are executed by a processor, the signal generating method described in the above method embodiment is implemented.

[0337] The computer-readable storage medium in the embodiments of the present disclosure is a computer instruction that can be sent, propagated or transmitted for use by or in conjunction with an instruction execution system, apparatus or device.

[0338] As one example, computer readable storage media are non-volatile storage media.

[0339] In some embodiments, more specific examples of computer-readable storage media in the present disclosure may include, but are not limited to: an electrical connection with one or more wires, a portable computer disk, a hard disk, a random access memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or flash memory), an optical fiber, a portable compact disk read-only memory (CD-ROM), an optical storage device, a magnetic storage device, a USB flash drive, a mobile hard disk, or any suitable combination of the foregoing.

[0340] In the embodiments of the present disclosure, the computer-readable storage medium may include a data signal propagated in a baseband or as a part of a carrier wave, in which computer instructions (readable program codes) are carried.

[0341] Such a propagated data signal may take a variety of forms, including but not limited to electromagnetic signals, optical signals, or any suitable combination of the foregoing.

[0342] In some examples, computing instructions contained on a computer-readable storage medium may be transmitted using any appropriate medium, including but not limited to wireless, wireline, optical fiber cable, RF, etc., or any suitable combination of the foregoing.

[0343] The embodiment of the present disclosure further provides a computer program product, which stores instructions. When the instructions are executed by a computer, the computer implements the signal generating method described in the above method embodiment.

[0344] The above instructions may be program codes. In specific implementation, the program codes may be written in any combination of one or more programming languages.

[0345] The programming language includes object-oriented programming languages, such as Java, C++, etc., and also includes conventional procedural programming languages, such as "C" language or similar programming languages.

[0346] The program code may execute entirely on the user's computing device, partly on the user's computing device, as a stand-alone software package, partly on the user's computing device and partly on a remote computing device or entirely on the remote computing device or server.

[0347] Where a remote computing device is involved, the remote computing device may be connected to the user computing device through any type of network, including a local area network (LAN) or a wide area network (WAN), or may be connected to an external computing device (e.g., through the Internet using an Internet service provider).

[0348] The embodiment of the present disclosure also provides a chip, including at least one processor and an interface;

[0349] An interface for providing program instructions or data to at least one processor;

[0350] At least one processor is used to execute program instructions to implement the signal generating method described in the above method embodiment.

[0351] In some embodiments, the chip may further include a memory, which is used to store program instructions and data, and the memory is located inside or outside the processor.

[0352] Those skilled in the art will appreciate that all or part of the steps for implementing the above embodiments may be implemented in the following forms, namely: a complete hardware implementation, a complete software implementation (including firmware, microcode, etc.), or a combination of hardware and software implementations, which may be collectively referred to herein as "circuits", "modules" or "systems".

[0353] Other embodiments of the disclosure will be apparent to those skilled in the art from consideration of the specification and practice of the invention disclosed herein.

[0354] The present disclosure is intended to cover any variation, use or adaptation of the present disclosure, which follows the general principles of the present disclosure and includes common knowledge or customary technical means in the technical field not disclosed in the present disclosure. The description and examples are to be regarded as exemplary only, and the true scope and spirit of the present disclosure are indicated by the appended claims.

Claims

1. A signal generation method, characterized in that: include: The OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal is broken up to obtain waveforms to be processed with different phases; Performing DFT transformation precoding or least squares LS optimization on waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed; A target frequency domain signal having the same frequency domain bandwidth as that of the LP-WUS signal is acquired based on the frequency domain signal.

2. The method according to claim 1, characterized in that The OOK waveform of the binary keying signal to be approximated generated based on the low-power wake-up LP-WUS signal is broken up to obtain waveforms to be processed with different phases, including: Generate an OOK waveform to be approximated based on the LP-WUS signal; Using a sequence with the same modulus value but different phases, the OOK waveform to be approximated is broken up to obtain an OOK waveform to be approximated with the same modulus value but different phases; Repeating the OOK waveform to be approximated with the same modulus but different phases according to a preset number to generate a plurality of OOK waveforms to be processed; Phase transformation is performed on each of the OOK waveforms to be processed according to different frequency domain mapping positions to obtain multiple waveforms to be processed with different phases.

3. The method according to claim 2, characterized in that The method of generating an OOK waveform to be approximated based on the LP-WUS signal comprises: Performing rate matching on the number of bits included in the LP-WUS signal according to the number of bits that can be carried by an orthogonal frequency division multiplexing (OFDM) symbol, so as to divide the LP-WUS signal into a plurality of signal blocks; Time domain expansion and OOK modulation are performed on each of the signal blocks to obtain an OOK waveform to be approximated corresponding to each of the signal blocks.

4. The method according to claim 3, characterized in that The performing time domain expansion and OOK modulation on each of the signal blocks comprises: The signal block is time-domain extended according to the number of sampling points corresponding to the DFT transform precoding or LS optimization, and the extended signal block obtained by the time-domain extension is OOK modulated to obtain the OOK waveform to be approximated.

5. The method according to claim 4, characterized in that The time domain expansion of the signal block according to the number of sampling points corresponding to the DFT transform precoding or LS optimization includes: When the waveform to be processed is subjected to DFT variation precoding, a signal block corresponding to each of the OFDM symbols is time-domain expanded according to the number of sampling points corresponding to the bandwidth size of the LP-WUS signal, and a portion of the OFDM symbol not covered by the extended signal is filled with zeros; When LS optimization is performed on the waveform to be processed, the signal blocks corresponding to each OFDM symbol are time-domain expanded according to the number of sampling points corresponding to the LS optimization, and the parts of the OFDM symbol not covered by the extended signal are filled with zeros.

6. The method according to claim 2, characterized in that The OOK waveform to be approximated is broken up by using a sequence with the same modulus value but different phases to obtain an OOK waveform to be approximated with the same modulus value but different phases, including: A sequence of phase rotation factors having the same modulus and phases changing according to a preset changing rule is used to perform phase rotation on the OOK waveform to be approximated, so as to obtain an OOK waveform to be approximated with the same modulus but different phases; or, A high-level ON waveform of the OOK waveform to be approximated is replaced by a constant modulus sequence to obtain an OOK waveform to be approximated with the same modulus value but different phase. The constant modulus sequence is a set of sequences with the same modulus value but different phase.

7. The method according to claim 6, characterized in that The OOK waveform to be approximated is phase rotated by using a sequence of phase rotation factors having the same modulus and phases changing according to a preset change rule to obtain an OOK waveform to be approximated with the same modulus but different phases, wherein the preset change rule includes: The phase changes by a preset interval amount, or the phase portion repeats and the phase of the non-repeating portion changes by a preset interval amount.

8. The method according to claim 7, characterized in that Before performing phase rotation on the OOK waveform to be approximated using a sequence of phase rotation factors having the same modulus and whose phases change according to a preset change rule, the method further includes: The sequence is constructed according to the phase rotation factor generated according to a preset variation rule.

9. The method according to claim 8, characterized in that When the preset change rule is that the phase changes at a preset interval, constructing the sequence according to the phase rotation factor generated according to the preset change rule includes: Determine a variation sequence according to a preset number of sampling points, the preset interval and a parameter corresponding to an OFDM symbol, and perform a modulo remainder operation on the variation sequence and a phase rotation parameter to obtain a phase rotation coefficient sequence; by is a phase rotation base, generates a plurality of phase rotation factors according to the phase rotation base and the phase rotation coefficient sequence, and constructs the sequence according to the phase rotation factors.

10. The method according to claim 8, characterized in that When the preset variation rule is that the phase part is repeated and the phase of the non-repeating part changes at a preset interval, constructing the sequence according to the phase rotation factor generated according to the preset variation rule includes: Determine a variation sequence according to a preset number of sampling points, the preset interval and a parameter corresponding to an OFDM symbol, and perform a modulo remainder operation on the variation sequence and a phase rotation parameter to obtain a phase rotation coefficient sequence; by is a phase rotation base, generates a plurality of phase rotation factors according to the phase rotation base and the phase rotation coefficient sequence, and constructs an initial sequence according to the phase rotation factors; The phase rotation factor to be repeated in the initial sequence is repeated according to a preset repetition amount to obtain the sequence.

11. The method according to claim 10, characterized in that The step of generating a plurality of phase rotation factors according to the phase rotation base and the phase rotation coefficient sequence, and constructing an initial sequence according to the phase rotation factors comprises: The sequence, the phase rotation basis, and the phase rotation coefficient sequence satisfy the relationship (1): Among them, α l (m i ) is the sequence; l is the index of the OFDM symbol; m i +r is the variation sequence; i is the variation index, which is a non-negative integer; N is the preset number of sampling points, which is an arbitrary positive integer; r is the parameter corresponding to the OFDM symbol, which is a non-negative integer; μ is the phase rotation parameter, which is an arbitrary positive number; p is the preset interval; m i modμ is the phase rotation coefficient sequence.

12. The method according to claim 11, characterized in that The method further comprises: When the indexes of the OFDM symbols are different, r corresponding to each of the OFDM symbols is 0; When the indexes of the OFDM symbols are different, r corresponding to each OFDM symbol is the index of the OFDM symbol; or When the indexes of the OFDM symbols are different, r corresponding to each OFDM symbol is an arbitrary value that is different from each other.

13. The method according to claim 11, characterized in that The preset number of sampling points is the number of sampling points corresponding to the ON waveform in the OOK waveform to be approximated or the number of sampling points in the OOK waveform to be approximated; the method further includes: When the preset number of sampling points is the number of sampling points corresponding to the ON waveform, When the preset number of sampling points is the number of sampling points in the OOK waveform to be approximated, in, is the number of bits contained in the extended signal block corresponding to the OFDM symbol, It is the number of bits carried by one OFDM symbol during rate matching.

14. The method according to claim 6, characterized in that The phase of the OOK waveform to be approximated is rotated by using a sequence of phase rotation factors having the same modulus and whose phases change according to a preset change rule, including: The waveform to be processed is obtained by multiplying the sequence of phase rotation factors with the OOK waveform to be approximated, or by multiplying the sequence of phase rotation factors with the high level ON waveform of the OOK waveform to be approximated.

15. The method according to claim 6, characterized in that The constant modulus sequence includes one or more of the following sequences: ZC sequence, random orthogonal amplitude modulation sequence, CGS sequence, low PAPR sequence.

16. The method according to claim 6, characterized in that The high-level ON waveform of the OOK waveform to be approximated is replaced by a constant modulus sequence to obtain an OOK waveform to be approximated with the same modulus value but different phase, including: Based on a preset substitution rule, a high-level ON waveform of the OOK waveform to be approximated is replaced by a constant modulus sequence to obtain an OOK waveform to be approximated with the same modulus value but different phase, wherein the preset substitution rule includes: The constant modulus sequence corresponding to each ON waveform is the same, the constant modulus sequence corresponding to each ON waveform is different, and the constant modulus sequences corresponding to some ON waveforms among the multiple ON waveforms are the same.

17. The method according to claim 2, characterized in that The preset number is smaller than the frequency domain bandwidth of the LP-WUS signal and is an integer multiple of the frequency domain bandwidth of the LP-WUS signal.

18. The method according to claim 2, characterized in that The phase transformation of the multiple OOK waveforms to be processed according to different frequency domain mapping positions to obtain multiple waveforms to be processed with different phases includes: Determine a starting frequency domain mapping position corresponding to each of the OOK waveforms to be processed, and determine a phase transformation sequence corresponding to the OOK waveform to be processed according to the starting frequency domain mapping position; Performing phase transformation on the corresponding OOK waveform to be processed according to the phase transformation sequence to obtain the waveform to be processed; The starting frequency domain mapping position is any RE in the OFDM symbol, and the phase transformation factors in the phase transformation sequence are continuous.

19. The method according to claim 18, characterized in that The determining of the starting frequency domain mapping position corresponding to each of the OOK waveforms to be processed, and determining the phase transformation sequence corresponding to the OOK waveform to be processed according to the starting frequency domain mapping position, comprises: Determine the starting frequency domain mapping position corresponding to each of the OOK waveforms to be processed according to the starting frequency domain mapping position corresponding to the OOK waveform to be processed with index 0, the index corresponding to each of the OOK waveforms to be processed, the preset number and the frequency domain bandwidth size of the LP-WUS signal; According to the phase transformation The starting frequency domain mapping position corresponding to the OOK waveform to be processed and the position index of each bit in the OOK waveform to be processed determine the phase transformation factor corresponding to each bit in the OOK waveform to be processed; The phase transformation sequence is constructed according to all phase transformation factors corresponding to the OOK waveform to be processed.

20. The method according to claim 18 or 19, characterized in that The step of performing phase transformation on the corresponding OOK waveform to be processed according to the phase transformation sequence to obtain the waveform to be processed includes: The waveform to be processed, the phase change sequence, and the OOK waveform to be processed satisfy the following relationship: in, is a matrix representation of the waveform to be processed; is the phase change sequence corresponding to the i-th OOK waveform to be processed; is the matrix representation of the i-th OOK waveform to be processed; i is the index of the OOK waveform to be processed; R is the frequency domain bandwidth of the LP-WUS signal; Q is the number of the OOK waveforms to be processed, which is a positive integer greater than 1; k c The index of the starting frequency domain mapping position of the OOK waveform to be processed with index 0; is the phase transformation basis; N is the total number of bits contained in the OOK waveform to be processed.

21. The method according to claim 18, characterized in that The step of performing phase transformation on the corresponding OOK waveform to be processed according to the phase transformation sequence to obtain the waveform to be processed includes: The waveform to be processed, the phase change sequence, and the OOK waveform to be processed satisfy the following relationship: in, is the signal in the waveform to be processed; is the signal in the OOK waveform to be processed; is a phase change sequence corresponding to the OFDM symbol with index l; i' is a position index corresponding to each signal on the OFDM symbol; k is the number of bits contained in the extended signal block corresponding to an OFDM symbol; c is the index of the starting frequency domain mapping position of the OOK waveform to be approximated, with index 0.

22. The method according to claim 21, characterized in that The least squares LS optimization is performed on the waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed, including: The waveform to be processed is subjected to LS optimization according to the truncation matrix, the inverse Fourier transform matrix, and the phase transformation sequence, wherein the frequency domain signal and the waveform to be processed, the truncation matrix, the inverse Fourier transform matrix, and the phase transformation sequence satisfy the relationship: in, is the frequency domain signal sequence corresponding to the i-th waveform to be processed, Each element in is a frequency domain signal mapped to different resource elements RE; is the truncation matrix constructed according to the frequency domain bandwidth of the LP-WUS signal; inv is the inverse Fourier transform matrix; F inv The conjugate transposed matrix of ; is the phase change sequence corresponding to the i-th OOK waveform to be processed; is the phase transformation basis; N is the number of sampling points, k c is the index of the starting frequency domain mapping position of the OOK waveform to be processed with an index of 0, and the starting frequency domain mapping position can be on any RE of any resource block RB.

23. The method according to claim 21, characterized in that The performing DFT transformation precoding on the waveforms to be processed with different phases to obtain a frequency domain signal corresponding to the waveforms to be processed includes: The frequency domain signal and the index of the OFDM symbol, the RE position index on the OFDM symbol, and the number of sampling points corresponding to the DFT transform precoding satisfy the relationship: Wherein, y(·) is the frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; The number of sampling points corresponding to the DFT transform precoding; is the phase-shifted signal block corresponding to the lth OFDM symbol.

24. The method according to claim 21, characterized in that The least squares LS optimization is performed on the waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed, including: The frequency domain signal and the index of the OFDM symbol, the RE position index on the OFDM symbol, the frequency domain bandwidth size of the LP-WUS signal, and the number of sampling points corresponding to the LS optimization satisfy the relationship: Wherein, y(·) is the frequency domain signal; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; Optimize the number of sampling points corresponding to the LS; is the frequency domain bandwidth of the LP-WUS signal; β is the power control factor; is the phase-shifted signal block corresponding to the lth OFDM symbol.

25. The method according to claim 1, characterized in that The number of the frequency domain signals is multiple; The acquiring, based on the frequency domain signal, a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal comprises: intercepting a header of each of the frequency domain signals to obtain a target frequency domain signal segment corresponding to each of the frequency domain signals; All the target frequency domain signal segments are sequentially spliced ​​to obtain the target frequency domain signal.

26. The method according to claim 25, characterized in that The step of intercepting the header of each of the frequency domain signals to obtain a target frequency domain signal segment corresponding to each of the frequency domain signals includes: intercepting the first 1 / Q part of each of the frequency domain signals to obtain the intercepted frequency domain signal segment; According to the power control factor β and power coefficient Processing the intercepted frequency domain signal segment to obtain the target frequency domain signal segment; Among them, Q is the number of OOK waveforms to be processed; the power control factor is used to ensure that the average value of the signal-to-noise ratio is the same as the signal-to-noise ratio in the physical downlink shared channel PDSCH; the power coefficient is used to ensure that the power of the target frequency domain signal corresponding to each of the frequency domain signal segments is equal to the power of the OOK waveform to be approximated.

27. The method according to claim 26, characterized in that The intercepting the first 1 / Q part of each of the frequency domain signals to obtain the intercepted frequency domain signal segment comprises: The intercepted frequency domain signal segment and the index of the waveform to be processed, the frequency domain signal corresponding to the waveform to be processed, and the number of the waveform to be processed satisfy the relationship: According to the power control factor β and the power coefficient Processing the intercepted frequency domain signal segment to obtain the target frequency domain signal segment includes: The target frequency domain signal segment and the intercepted frequency domain signal segment satisfy the relationship: in, is the target frequency domain signal segment; X i is the intercepted frequency domain signal segment; i is the index of the waveform to be processed; Q is the number of the waveform to be processed; R is the frequency domain bandwidth size of the LP-WUS; β is the power control factor; is the phase transformation basis, N is the number of sampling points; k c is the index of the starting frequency domain mapping position corresponding to the 0th waveform to be processed.

28. The method according to claim 25, characterized in that The step of intercepting the header of each of the frequency domain signals to obtain a target frequency domain signal segment corresponding to each of the frequency domain signals includes: The target frequency domain signal segment and the index of the OFDM symbol, the RE position index on the OFDM symbol, and the number of sampling points corresponding to the DFT transform precoding satisfy the relationship: Wherein, y(·) is the frequency domain signal in the target frequency domain signal segment; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; The number of sampling points corresponding to the DFT transform precoding; is the phase transformation signal block corresponding to the OFDM symbol with index l; Q is the total number of frequency domain signals generated by DFT transform precoding; m is the index of the frequency domain signal corresponding to the OFDM symbol with index l.

29. The method according to claim 25, characterized in that The step of intercepting the header of each of the frequency domain signals to obtain a target frequency domain signal segment corresponding to each of the frequency domain signals includes: The target frequency domain signal segment and the index of the OFDM symbol, the RE position index on the OFDM symbol, the frequency domain bandwidth size of the LP-WUS signal, and the number of sampling points corresponding to the LS optimization satisfy the relationship: Wherein, y(·) is the frequency domain signal in the target frequency domain signal segment; l is the index of the OFDM symbol, which ranges from Increasing in sequence; k is the index of the RE position in the OFDM symbol with index l, and its value ranges from i is the signal index in the extended signal block corresponding to the OFDM symbol with index l, and its value ranges from Increasing in sequence; Optimize the number of sampling points corresponding to the LS; is the frequency domain bandwidth of the LP-WUS signal; β is the power control factor; is the phase transformation signal block corresponding to the lth OFDM symbol; Q is the total number of frequency domain signals generated by the LS optimization; m is the index of the frequency domain signal corresponding to the OFDM symbol with index l.

30. The method according to any one of claims 25 to 29, characterized in that The step of sequentially splicing all the target frequency domain signal segments to obtain the target frequency domain signal includes: All the target frequency domain signal segments are sorted and spliced ​​according to the starting frequency domain mapping positions corresponding to the target frequency domain signal segments to obtain the target frequency domain signal.

31. The method according to claim 1, characterized in that The method further comprises: A target transmission signal is generated based on the frequency domain signal.

32. The method according to claim 31, characterized in that The generating a target transmission signal based on the frequency domain signal comprises: Mapping the frequency domain signal corresponding to the RE on each OFDM symbol to the RE in the OFDM modulator; The frequency domain signal is OFDM modulated by the OFDM modulator to obtain a target OOK waveform that is close to the OOK waveform to be approximated, and the target transmission signal is constructed according to the target OOK waveform.

33. The method according to claim 31, characterized in that The method further comprises: The target transmission signal is transmitted to a wake-up signal receiver in a user terminal UE through a multipath fading channel, and the target transmission signal is envelope-detected by the wake-up signal receiver to obtain the LP-WUS signal, and the main wireless module is awakened based on the LP-WUS signal.

34. A signal generating device, characterized in that: include: A waveform processing module, used for breaking up the OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal to obtain a waveform to be processed with different phases; An optimization module, used for performing DFT transform precoding or least squares LS optimization on the waveform to be processed to obtain a frequency domain signal corresponding to the waveform to be processed; A frequency domain processing module is used to obtain a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal.

35. A communication system, characterized in that: include: The base station is used to break up the OOK waveform of the binary keying signal to be approximated generated based on the low power wake-up LP-WUS signal to obtain a waveform to be processed with different phases; Performing DFT transformation precoding or least squares LS optimization on waveforms to be processed with different phases to obtain frequency domain signals corresponding to the waveforms to be processed; Acquire a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal; Acquire a target frequency domain signal having the same frequency domain bandwidth as the LP-WUS signal based on the frequency domain signal, and generate a target transmission signal based on the frequency domain signal; The user terminal includes a wake-up signal receiver and a main wireless module; the wake-up signal receiver is used to perform envelope detection on the received target transmission signal, obtain the LP-WUS signal, and wake up the main wireless module according to the LP-WUS signal; the main wireless module is used to communicate wirelessly with the base station.

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