Full-duplex short-distance point-to-point millimeter wave communication system and method

Abstract

The invention mainly relates to the technical field of millimeter wave communication, provides a full-duplex short-distance point-to-point millimeter wave communication system and method, and aims to overcome leakage interference caused by emission signal leakage and realize full-duplex short-distance point-to-point millimeter wave communication transmission on the premise of performing signal transceiving control without depending on an external system. The method is characterized in that a phase shift calibrator and a phase shifter are arranged, the phase shift calibrator calculates a phase shift value of the phase shifter according to the strength of a self-interference signal and a set phase calibration strategy and writes the phase shift value into the phase shifter, and the phase shifter adjusts the initial phase of a local oscillator signal generated by a local oscillator to ensure that the initial phase is orthogonal to the initial phase of the self-interference signal; the self-interference signal energy is located on two times of carrier frequency and is suppressed by band-pass filtering, and the target signal sent by the opposite node is obtained through subsequent wave shaping, so that the target signal sent by the opposite node can still be stably and reliably demodulated from strong interference in a full-duplex simultaneous transceiving mode.

Description

Technical Field

[0001] This invention relates to the field of millimeter-wave communication technology, and in particular to a full-duplex short-range point-to-point millimeter-wave communication system and method. Background Technology

[0002] With the increasing demand for short-range, high-speed data interaction, millimeter-wave communication technology is commonly used in ultra-short-range (a few centimeters) point-to-point communication to eliminate the need for physical cables and connectors. Inexpensive short-range point-to-point millimeter-wave communication often employs on-off keying modulation (OOK modulation) to simplify system complexity and power consumption. Therefore, its application in wireless scenarios for wired interfaces such as USB, Ethernet, HDMI, and UART is becoming increasingly widespread. For example, patents CN204559736U and CN118316770A, as well as STMicroelectronics' ST60A3 product, all utilize this solution. However, OOK modulation has inherent technical drawbacks:

[0003] (1) Its transmitted signal has serious energy leakage in the frequency domain, and the generated spurious radiation is difficult to meet the strict radio regulations. Usually, additional spurious suppression filters need to be introduced in the transmission path, which increases the cost and design complexity of the system.

[0004] (2) Existing OOK communication solutions generally use Time Division Duplex (TDD) mode to achieve bidirectional communication. TDD mode requires communication nodes to switch between transmit and receive states at high speed. Therefore, the system must rely on an external main control chip to provide a clear transmit and receive status control signal for interface adaptation. However, most existing wired interface standards do not define such transmit and receive control signals, requiring existing systems to perform interface adaptation in terms of transmit and receive status control, which presents significant obstacles in the application ecosystem;

[0005] (3) In addition, existing wired interfaces are usually full-duplex communication, that is, data is transmitted and received simultaneously. For example, USB 3.0 uses two paths, Tx data line and Rx data line, to achieve full-duplex transmission. For millimeter wave communication, if transmission and reception are carried out simultaneously, it will inevitably cause self-interference problems caused by leakage of the transmitted signal to the receiving path. In the millimeter wave band, this problem is particularly prominent. However, existing interference suppression technologies are often complex and expensive. For example, self-interference cancellation technology is difficult to apply in low-cost, low-power short-range communication scenarios.

[0006] Therefore, there is an urgent need for a millimeter-wave communication system and method that can achieve full-duplex communication without relying on external transmit / receive control signals, effectively suppress transmit leakage interference, and have flexible spurious radiation control capabilities. Summary of the Invention

[0007] The technical problem to be solved by this invention is to provide a full-duplex short-range point-to-point millimeter-wave communication system and method, with the aim of overcoming the leakage self-interference problem caused by the leakage of transmitted signals without relying on external systems for signal transmission and reception control, and realizing full-duplex short-range point-to-point millimeter-wave communication transmission.

[0008] The technical solution adopted by the present invention to solve the above-mentioned technical problems is as follows:

[0009] On one hand, the present invention provides a full-duplex short-range point-to-point millimeter-wave communication system, the system comprising:

[0010] The local oscillator is used to generate carrier signals for the signal transmitting module and local oscillator signals for the signal receiving module.

[0011] The signal transmission module is used to modulate the wired waveform emitted by the current node onto the carrier signal to generate a modulated signal, wherein the modulated signal adopts amplitude modulation.

[0012] The amplification and radiation unit, connected to the signal transmission module, is used to radiate the modulated signal into the environment and receive the millimeter-wave electromagnetic signal in the environment. The millimeter-wave electromagnetic signal in the environment is a composite signal of the self-interference signal generated based on the leakage of the modulated signal and the target signal emitted by the counterpart node.

[0013] A phase shift calibrator and a phase shifter, wherein the phase shift calibrator is used to calculate the phase shift value of the phase shifter based on the self-interference signal strength and the set phase calibration strategy, and the phase shifter is used to adjust the phase of the local oscillator signal based on the phase shift value;

[0014] The signal receiving module suppresses self-interference signals in the synthesized signal based on the phase-adjusted local oscillator signal, and then performs rectification on the interference-suppressed signal to obtain the target signal.

[0015] Furthermore, the signal transmission module includes an up-conversion mixer, which is used to modulate the wired waveform emitted by the current node onto the carrier signal generated by the local oscillator to generate a modulated signal.

[0016] Furthermore, the signal transmission module also includes a depolarizer, which is used to convert the bipolar code-shaped wired waveform into a unipolar code waveform.

[0017] Furthermore, the signal transmission module also includes a spurious suppressor, which is used to filter out high-frequency components of the unipolar code waveform.

[0018] Furthermore, the phase calibration strategy of the phase shift calibrator is as follows: the phase shift calibrator obtains the phase shift value that minimizes the average power value based on the average power value of the envelope wave detection signal in the signal receiving module using the ergonomic selection method, gradient descent method or bisection method, and writes the phase shift value into the phase shifter.

[0019] Furthermore, the signal receiving module includes a down-conversion mixer, a bandpass filter, and an envelope detector; the down-conversion mixer is used to receive the synthesized signal generated by the amplification and radiation unit and the local oscillator signal after phase adjustment by the phase shifter, and down-converts the synthesized signal to the intermediate frequency. After the bandpass filter extracts the intermediate frequency signal, the envelope detector performs envelope detection on the intermediate frequency waveform to obtain the envelope waveform.

[0020] Furthermore, the signal receiving module also includes a binary quantization module, which includes a threshold generator and a decision unit. The threshold generator is used to generate a voltage decision threshold, and the decision unit is used to compare the envelope waveform with the voltage decision threshold and output the target signal.

[0021] The threshold generator generates voltage decision thresholds including: after DC blocking filtering of the envelope waveform, using zero voltage as the decision threshold, or obtaining the average value of historical envelope values ​​as the decision threshold.

[0022] Furthermore, the amplification and radiation unit includes an antenna, a power amplifier, and a low-noise amplifier; the antenna is a planar end-fire antenna, a slot antenna, or a planar side-fire antenna; wherein the transmitting and receiving antennas are orthogonally polarized split antennas or high-isolation dual-polarized antennas.

[0023] Furthermore, the difference between the carrier frequencies of the modulated signal and the target signal is not less than [amount missing]. ,in It is the symbol period of the modulated signal. It is the symbol period of the target signal.

[0024] Furthermore, the polarization directions of the modulated signal and the target signal are orthogonal.

[0025] On the other hand, the present invention also provides a full-duplex short-range point-to-point millimeter-wave communication method, the method comprising:

[0026] The phase shift calibrator calculates the phase shift value of the phase shifter based on the self-interference signal strength and the set phase calibration strategy, and configures the phase shifter based on the calculated phase shift value;

[0027] The signal transmission module modulates the wired waveform emitted by the current node onto a carrier signal to generate a modulated signal; the amplification and radiation unit radiates the modulated signal into the environment, and generates a composite signal by superimposing the self-interference signal generated by the modulated signal onto the target signal emitted by the other node.

[0028] The signal receiving module uses the local oscillator signal after phase adjustment by the phase shifter to suppress the self-interference signal in the synthesized signal, and then performs rectification on the interference-suppressed signal to obtain the target signal.

[0029] Furthermore, the method also includes: after the phase shifter is calibrated during cold start, the phase of the phase shifter remains constant, or compensation adjustment is performed based on the drift of the phase value caused by temperature changes.

[0030] The beneficial effects of this invention are as follows: It only requires the use of the full-duplex short-range point-to-point millimeter-wave communication system and wired interface described in this invention for data path connection, without the need for other interfaces and system adaptations. It realizes full-duplex seamless transmission of the wired interface and can automatically and accurately search for and lock the optimal phase point. It effectively cancels the strong leakage interference generated by its own transmitted signal in the signal receiving module, thereby ensuring that even in full-duplex simultaneous transmit and receive mode, it can still stably and reliably demodulate the weak useful signal from the other party from strong interference, which can help expand the application of short-range point-to-point millimeter-wave communication technology. Attached Figure Description

[0031] Figure 1 This is a schematic diagram of a point-to-point millimeter-wave wireless communication link;

[0032] Figure 2 This is a logic block diagram of the transmit and receive paths in a millimeter-wave communication node.

[0033] Figure 3 This is a schematic diagram of a full-duplex short-range point-to-point millimeter-wave communication system.

[0034] Figure 4 A block diagram of the amplified radiation unit structure;

[0035] Figure 5 The logic structure diagram for generating voltage decision thresholds based on filtering method for the binary quantization module;

[0036] Figure 6 The logic structure diagram for generating voltage decision thresholds for the binary quantization module based on the threshold estimation method is shown. Detailed Implementation

[0037] The core of the full-duplex short-range point-to-point millimeter-wave communication system and method adopted by this invention to solve the above-mentioned technical problems is that signal transmission and signal reception occur simultaneously in full-duplex transmission. When the current node radiates a signal into the environment through the amplification and radiation unit, the amplification and radiation unit also receives the target signal of the other node from the environment. In the process of receiving the target signal of the other node, the amplification and radiation unit will inevitably receive the transmitted signal radiated into the environment at the same time, forming leakage self-interference from transmission to reception. Leakage self-interference is usually formed inside the circuit or structure, and its intensity is much greater than the target signal intensity transmitted by the other node. In order to suppress this strong leakage self-interference, this invention uses a phase shift calibrator to calculate the phase shift value of the phase shifter according to the self-interference signal intensity and the set phase calibration strategy. After writing the phase shift value into the phase shifter, the phase shifter is calibrated. The phase shifter adjusts the initial phase of the local oscillator signal generated by the local oscillator according to the calibrated phase to ensure that this initial phase is orthogonal to the initial phase of the self-interference signal. The energy of the self-interference signal will be located at twice the carrier frequency and suppressed by bandpass filtering. After subsequent rectification, the target signal sent by the other node can be obtained.

[0038] To enable those skilled in the art to better understand the present invention, the solutions in this embodiment will be clearly and completely described below with reference to the accompanying drawings.

[0039] Figure 1 This diagram illustrates a typical application scenario of the full-duplex short-range point-to-point millimeter-wave communication system of the present invention. The communication link in this typical application scenario includes two communication nodes (wired interface #1 and wired interface #2)—the current node and the other node. The two communication nodes establish an input and output connection (millimeter-wave communication node #1 and millimeter-wave communication node #2) through the full-duplex short-range point-to-point millimeter-wave communication system described in this invention, replacing the traditional physical wired interface. The carrier frequencies between the two communication nodes are different, preferably differing by no less than [amount missing]. , It is the period of the binary level of the input waveform at the current node Tx, that is, the symbol period of the modulation signal at the current node. It is the period of the binary level of the input waveform of the other node, that is, the symbol period of the target signal of the other node.

[0040] The full-duplex short-range point-to-point millimeter-wave communication system described in this invention is as follows: Figure 2 As shown, it includes a local oscillator (OL), a signal transmission module, a radiation amplification unit, a phase shifter calibrator, a phase shifter, and a signal receiving module.

[0041] The local oscillator (LO) is used to generate a carrier signal for the signal transmitting module and a local oscillator signal for the signal receiving module (the carrier signal and the local oscillator signal are the corresponding signal names of the signal generated by the LO in the signal transmitting module and the signal receiving module, respectively). The signal transmitting module is used to modulate the waveform (Tx) of the current node onto the carrier signal to generate a modulated signal. The amplification and radiation unit is connected to the signal transmitting module and is used to receive a composite signal generated from the self-interference signal generated based on the modulated signal and the target signal emitted by the other node. The phase shift calibrator is used to calculate the phase shift value of the phase shifter according to the self-interference signal strength and the set phase calibration strategy. The phase shifter adjusts the phase of the LO signal according to the phase shift value. The signal receiving module suppresses the self-interference signal in the composite signal based on the phase-adjusted LO signal and performs rectification on the interference-suppressed signal to obtain an output waveform (Rx), which is the target signal emitted by the other node.

[0042] like Figure 3 As shown, the signal transmission module includes an up-conversion mixer (TxMixer). The signal from the current node is a binary level signal from wired interfaces such as USB and HDMI, containing only two active levels. Common wired interfaces use both unipolar and bipolar codes. If the wired interface served by the system uses a bipolar code and the input signal is a differential waveform, a polarity depolarizer is needed to convert it to unipolar code. Therefore, in this case, the signal transmission module also includes a polarity depolarizer. The polarity depolarizer can be implemented using a high-speed voltage comparator. Its implementation logic is as follows: if the differential waveform is a positive voltage, output a high level; if it is a negative voltage, output a low level. If the low-level voltage is greater than zero, it is called a bias unipolar code, and the low-level voltage is called the bias voltage.

[0043] The spectral leakage of unipolar codes is defined by the sinc function. In order to meet the requirements of radio regulations for spurious radiation, a spurious suppressor can be set up for band-limited filtering as needed. From a cost perspective, the spurious suppressor is implemented using a passive filter of order 2 to 4 to suppress the energy of the sidelobe of the sinc function in the frequency domain, ensuring that the radiated signal meets the requirements of FCC and other regulations.

[0044] The output signal of the spurious suppressor is up-converted to the radio frequency by the carrier signal generated by the local oscillator in the up-conversion mixer, generating a modulation signal, which enters the amplification and radiation unit. The amplification and radiation unit amplifies the modulation signal and radiates it into the environment. At the same time, the amplification and radiation unit also continuously receives electromagnetic wave signals. The received electromagnetic wave signals are composite signals, which specifically include two parts: one part is the target signal from the other party node, and the other part is the self-interference signal generated based on the leakage of the modulation signal.

[0045] like Figure 4As shown, the amplification and radiation unit includes an antenna, a power amplifier (PA), and a low-noise amplifier (LNA), wherein the power amplifier and the low-noise amplifier are optional components. The antenna in the amplification and radiation unit is a planar end-fire antenna, a slot antenna, or a planar side-fire antenna; wherein the transmitting and receiving antennas are orthogonally polarized split antennas or high-isolation dual-polarized antennas.

[0046] To suppress self-interference signals, a phase shifter and a phase shifter are set between the local oscillator and the signal receiving module. The phase shifter continuously samples the envelope waveform at the signal receiving module end, evaluates the interference intensity of the self-interference signal, and calculates the phase shift value of the phase shifter based on the interference intensity and the set phase calibration strategy.

[0047] The phase shift calibrator calculates the average power value of the envelope wave detection signal, and uses the ergonomic selection method, gradient descent method or bisection method to obtain the phase shift value that minimizes the average power value as the optimal phase shift value, and then configures the optimal phase shift value to the phase shifter.

[0048] Specifically, obtaining the optimal phase shift value using the bisection method involves: the phase shifter calibrator controlling the phase shifter in its adjustable phase range (e.g., 0° to 360°) at the midpoint (180°) configuration, measuring and recording the envelope average power value V_avg1; then, measurements are taken at two phase points, 90° and 270°, to obtain V_avg2 and V_avg3. By comparing V_avg1, V_avg2, and V_avg3, the optimal phase point that minimizes the average power value can be determined within a 90° interval. Subsequently, a bisection search is performed again within the interval selected in the previous step. This process is iterated until the difference between the average power values ​​of two consecutive measurements is less than a preset threshold (e.g., the amplitude change corresponding to a 1° phase change). At this point, the optimal phase point is considered to have been found, and the phase shifter is locked in this configuration.

[0049] Specifically, obtaining the optimal phase shift value using the traversal selection method includes: traversing all preset phase shifter phases, measuring the average power value of the envelope signal under each configuration, selecting the phase with the smallest average power value of the envelope signal as the optimal phase point after the traversal is completed, and locking the phase shifter to this configuration.

[0050] Preferably, phase shifter calibration is performed during cold start to obtain the optimal phase shift value. During phase shifter calibration, the depolarizer maintains a constant high output level, while ensuring that the phase shifter calibrator is not interfered with by signals from the other node or other factors. During the phase shifter calibration phase, the expression for the self-interference signal is: Where A(t) is the transmitted waveform, f c It is the carrier frequency. It is the initial phase of the self-interference signal. This is the propagation delay of the self-interference signal; the expression for the local oscillator signal after phase adjustment by the phase shifter is: ,in It is the initial phase of the carrier signal after being adjusted by the phase shifter.

[0051] like Figure 3 As shown, the signal receiving module includes a down-conversion mixer (RxMixer), a bandpass filter, an envelope detector, and a binary quantization module. The output signal of the down-conversion mixer is: In the equation, the first term on the right side is at twice the carrier frequency and is suppressed by the bandpass filter, while the second term is at zero frequency. The phase configuration via the phase shifter ensures that... This energy approaching zero can be achieved by adjusting the phase shift value of the phase shifter, meaning that self-interference signals can be suppressed. The binary quantization module is an optional component in the signal receiving module, and its function is to output a definite binary level signal.

[0052] Lock the phase of the phase shifter to During the communication between the current node and the other node, the downconverter mixer mixes the synthesized signal and the local oscillator signal whose phase has been adjusted by the phase shifter. The high-frequency components are filtered out by the bandpass filter. After downconversion, the intermediate frequency waveform is obtained. After the bandpass filter extracts the intermediate frequency signal, the envelope detector performs envelope detection on the intermediate frequency waveform to obtain the envelope waveform. The binary quantization module performs binarization processing on the envelope wave to obtain the target signal.

[0053] Ideally, the upper and lower cutoff frequencies of the bandpass filter should be as close as possible to the edge of the signal sent from the other node in order to achieve the best suppression of leakage self-interference, blocking interference, noise, etc., and obtain the purest intermediate frequency received signal.

[0054] The binary quantization module includes a threshold generator and a decision unit. The threshold generator generates a voltage decision threshold, and the decision unit compares the envelope waveform with the decision threshold and outputs a target signal. The threshold generator generates the voltage decision threshold as follows: Figure 5 As shown, after DC blocking filtering of the envelope waveform, zero voltage is used as the voltage decision threshold, or as... Figure 6 As shown, the average power value of the historical envelope is used as the voltage decision threshold. The output of the binary decision can be selected as either bipolar or unipolar output to adapt to the electrical characteristics requirements of the wired interface.

[0055] Preferably, after phase calibration during cold start, the optimal phase of the phase shifter can be kept constant, or it can be compensated for based on the drift of the phase value as the temperature changes.

[0056] Example: This example uses USB 3.1 as an example to further explain the full-duplex short-range point-to-point millimeter-wave communication system and method described in this invention.

[0057] USB 3.1 has two differential pairs, called Tx differential pairs and Rx differential pairs. The former is connected to the Tx port of the system, and the latter is connected to the Rx port of the system.

[0058] Cold start calibration: After a cold start, phase shifter calibration is performed first. Specifically, the phase shifter calibrator controls the depolarizer to output a high level, traversing all phase shifter settings and measuring the average power value of the envelope waveform under each setting. The phase shifter setting with the lowest average power value is selected as the phase shifter calibration result. After writing the phase calibration result into the phase shifter, the calibration process ends.

[0059] After both USB A and USB B devices have completed boot calibration, the process of USB A sending data to USB B is as follows:

[0060] The output signal flow of a USB A device is as follows: The signal waveform on the Tx differential pair of USB 3.1 is a bipolar code. It is converted into a unipolar code waveform by a depolarizer. The unipolar code waveform is sent to a spurious suppressor to filter out high-frequency components to prevent electromagnetic radiation from exceeding regulatory requirements (at this time, the output of the spurious suppressor is no longer a binary level). The output of the spurious suppressor enters the upconversion mixer and is upconverted to the carrier frequency by the local oscillator to generate a modulated signal, which is then released into the environment through the amplification and radiation unit.

[0061] The process of receiving signals by a USB B device is as follows: The amplification and radiation unit receives the synthesized signal from the environment. The synthesized signal enters the downconverter mixer, which mixes the synthesized signal with the local oscillator signal whose phase has been adjusted by the phase shifter. High-frequency components are filtered out by the bandpass filter. The envelope detector performs envelope detection on the intermediate frequency waveform to obtain the envelope waveform. The envelope waveform is input to the binary quantization module, which performs DC blocking filtering on the envelope waveform. The waveform output by the DC blocking filter is restored to a binary level signal. If it is a positive level, a positive voltage is applied to the Rx differential line of the USB 3.1; if it is a negative level, a negative voltage is applied to the Rx differential line of the USB 3.1.

[0062] The process of a USB B device sending data to a USB A device is the same as above, and will not be explained in detail here.

Claims

1. A full-duplex short-range point-to-point millimeter-wave communication system, characterized in that, The system includes: The local oscillator is used to generate carrier signals for the signal transmitting module and local oscillator signals for the signal receiving module. The signal transmission module is used to modulate the wired waveform emitted by the current node onto the carrier signal to generate a modulated signal, wherein the modulated signal adopts amplitude modulation. The amplification and radiation unit, connected to the signal transmission module, is used to radiate the modulated signal into the environment and receive the millimeter-wave electromagnetic signal in the environment. The millimeter-wave electromagnetic signal in the environment is a composite signal of the self-interference signal generated based on the leakage of the modulated signal and the target signal emitted by the counterpart node. A phase shift calibrator and a phase shifter, wherein the phase shift calibrator is used to calculate the phase shift value of the phase shifter based on the self-interference signal strength and the set phase calibration strategy, and the phase shifter is used to adjust the phase of the local oscillator signal based on the phase shift value; The signal receiving module suppresses self-interference signals in the synthesized signal based on the phase-adjusted local oscillator signal, and then performs rectification on the interference-suppressed signal to obtain the target signal.

2. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 1, characterized in that, The signal transmission module includes an up-conversion mixer, which is used to modulate the wired waveform emitted by the current node onto the carrier signal generated by the local oscillator to generate a modulated signal.

3. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 2, characterized in that, The signal transmission module also includes a depolarizer, which is used to convert a bipolar code-shaped wired waveform into a unipolar code waveform.

4. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 2, characterized in that, The signal transmission module also includes a spurious suppressor, which is used to filter out high-frequency components of the unipolar code waveform.

5. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 1, characterized in that, The phase calibration strategy of the phase shift calibrator is as follows: the phase shift calibrator uses the ergonomic selection method, gradient descent method or bisection method to obtain the phase shift value that minimizes the average power value based on the average power value of the envelope wave detection signal in the signal receiving module, and writes the phase shift value into the phase shifter.

6. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 1, characterized in that, The signal receiving module includes a down-conversion mixer, a bandpass filter, and an envelope detector. The down-conversion mixer is used to receive the synthesized signal generated by the amplification and radiation unit and the local oscillator signal after phase adjustment by the phase shifter, and down-converts the synthesized signal to the intermediate frequency. After the bandpass filter extracts the intermediate frequency signal, the envelope detector performs envelope detection on the intermediate frequency waveform to obtain the envelope waveform.

7. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 6, characterized in that, The signal receiving module further includes a binary quantization module, which includes a threshold generator and a decision unit. The threshold generator is used to generate a voltage decision threshold, and the decision unit is used to compare the envelope waveform with the voltage decision threshold and output the target signal. The threshold generator generates voltage decision thresholds including: after DC blocking filtering of the envelope waveform, using zero voltage as the decision threshold, or obtaining the average value of historical envelope values ​​as the decision threshold.

8. The full-duplex short-range point-to-point millimeter-wave communication system according to claim 1, characterized in that, The amplification and radiation unit includes an antenna, a power amplifier, and a low-noise amplifier; the antenna is a planar end-fire antenna, a slot antenna, or a planar side-fire antenna; wherein the transmitting and receiving antennas are orthogonally polarized split antennas or high-isolation dual-polarized antennas.

9. The full-duplex short-range point-to-point millimeter-wave communication system according to any one of claims 1-8, characterized in that, The difference between the carrier frequencies of the modulating signal and the target signal is not less than ,in It is the symbol period of the modulated signal. It is the symbol period of the target signal.

10. The full-duplex short-range point-to-point millimeter-wave communication system according to any one of claims 1-8, characterized in that, The polarization directions of the modulating signal and the target signal are orthogonal.

11. A full-duplex short-range point-to-point millimeter-wave communication method, applied to the full-duplex short-range point-to-point millimeter-wave communication system according to any one of claims 1-10, characterized in that, The method includes: The phase shift calibrator calculates the phase shift value of the phase shifter based on the self-interference signal strength and the set phase calibration strategy, and configures the phase shifter based on the calculated phase shift value; The signal transmission module modulates the wired waveform emitted by the current node onto the carrier signal to generate a modulated signal; The amplification and radiation unit radiates the modulated signal into the environment, and generates a composite signal by superimposing the self-interference signal generated by the modulated signal with the target signal emitted by the counterpart node. The signal receiving module uses the local oscillator signal after phase adjustment by the phase shifter to suppress the self-interference signal in the synthesized signal, and then performs rectification on the interference-suppressed signal to obtain the target signal.

12. The full-duplex short-range point-to-point millimeter-wave communication method according to claim 11, characterized in that, The method further includes: after the phase shifter is calibrated during cold start, the phase of the phase shifter remains constant, or compensation adjustment is made based on the drift of the phase value caused by temperature change.

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