LED light intensity continuously variable stabilizer

Abstract

LED light intensity continuously variable stabilizer is a switching DC stabilized power supply that drives LED lights to emit light. The ratio of its rated output power to the minimum output power is greater than 30, and the user can continuously adjust the output power of this device within this wide range, so that the luminous intensity of the LED lamp is suitable for the illumination required by the home living environment. In turn, the types of indoor lighting fixtures can be reduced and the lighting circuit can be simplified. In this device: the applied advanced control technology and ultra-high-speed negative feedback control technology have expanded a very broad world for the application of switching DC stabilized power supply in self-excited oscillation flyback mode; the applied switching process acceleration technology can not only reduce switching losses, but also increase the range of changes in system output power; the applied storage charge rapid elimination technology can reduce both switching losses and reverse bias losses of the switch tube; the applied oscillation start-up technology can not only reduce switching losses, but also reduce forward bias losses of the switch tube.

Description

[0001] The first time a term appears in this manual, it is presented in bold. Technical Field The invention belongs to lighting electrical equipment, and is a system which uses a switching type DC stable power supply in a self-excited oscillation working mode to drive an LED lamp to emit light. Background Art In order to adapt to unstable input power and improve the efficiency of power supply, people have developed pulse width modulation switching DC regulated power supply. This type of power supply has high efficiency when the load power is large, but low efficiency when the load power is small, so it is suitable for use in systems with large load power but little change.

[0002] In view of the shortcomings of pulse width modulation switching power supply, people have developed pulse frequency modulation switching DC regulated power supply. This type of power supply has high efficiency when the load power is small, but it is not suitable for use in systems with large load power.

[0003] Combining the advantages of the above two switching power supplies, people have developed a pulse width frequency modulation switching DC regulated power supply; trying to have all the advantages of large output power, large output power range and high power conversion efficiency. However, to adjust the luminous flux radiated by LED lamps to meet people's living needs, not only a stable DC power supply is required, but also a very large ratio of the rated output power to the minimum output power of the power supply is required, and the power supply has a high power conversion efficiency at each output power point. However, when this pulse width frequency modulation switching power supply works in "PWM" mode, the efficiency of power conversion also decreases as the output power decreases; only when its output power drops to a certain level, it automatically switches to "PFM" mode, and it is difficult for this power supply to ensure that the brightness of the LED lamp does not flicker during the switching mode, and it is also difficult to ensure that the luminous intensity of the LED lamp does not change suddenly after the switching mode.

[0004] In the development process of switching DC regulated power supply, a self-excited intermittent oscillation switching DC regulated power supply was once widely used in cathode ray tube color TV sets; in addition, there is a self-excited oscillation switching DC regulated power supply, which is also widely used. Although these two classic self-excited (intermittent) oscillation switching power supplies are also very efficient, due to their outdated control technology, it is difficult to make the ratio of rated output power to minimum output power exceed 10:1, so these two switching power supplies cannot be used to adjust the light intensity of LED lamps.

[0005] The purpose of the invention is to develop an LED lamp driving device suitable for the illumination required by people's home living environment. The device can not only make the LED lamp stably radiate the rated luminous flux, but also the user can arbitrarily adjust the size of the stable luminous flux radiated by the LED lamp, that is, to develop a stable driver that can continuously change the luminous intensity of the LED lamp within a large range. BRIEF DESCRIPTION OF THE DRAWINGS In order to have a deeper understanding of the features of the present invention, four drawings are provided as follows:

[0006] Figure 1 Block diagram of LED light intensity continuously variable stabilizer;

[0007] Figure 2 Block diagram of the variable current state detector;

[0008] Figure 3 The simplest circuit diagram of LED light intensity continuously variable stabilizer;

[0009] Figure 4 The simplest circuit diagram of the inverter state controller. Summary of the invention The classic single-tube self-oscillation flyback mode switching DC regulated power supply is decomposed, and the reason why the ratio of its rated output power to the minimum output power is difficult to exceed 10:1 is analyzed. The passive positive feedback simple branch in the circuit is reformed into an active positive feedback multifunctional network. Thus, a novel self-oscillation flyback mode switching DC regulated power supply is explored - LED light intensity continuously variable stabilizer, whose rated output power to minimum output power ratio exceeds 30:1, which is enough to meet the illumination requirements of people's home living environment.

[0010] Because LED is a non-negative resistance device, the present invention can adopt both the current stabilization and voltage limiting working mode and the voltage stabilization and current limiting working mode. Regardless of which working mode is adopted, the components of the present invention are the same, and even the specific circuit diagram is the same. In practice, the working mode of the present invention can be changed by adjusting the parameters of three (two) components; in fact, when the LED lamp is close to the rated working state, automatic adjustment actions of both current stabilization and voltage stabilization often occur at the same time. Therefore, the macro structure and working principle of the present invention to be explained below are suitable for both the current stabilization and voltage limiting working mode and the voltage stabilization and current limiting working mode.

[0011] Section 1 The present invention uses the classic input power converter 1, LED lamp 6, potential signal converter 3, current signal converter 4, transforms the flyback switch type transducer 5, and creates the original variable current state detector 2 and other six components (see Figure 1 ).

[0012] The connection method of each component in the present invention is: the mains is connected to the input end of the input power converter 1; the Ec terminal of the input power converter 1 is connected to the positive electrode of the working power supply of the flyback switch type transducer 5 and the St terminal of the current conversion state detector 2; the Ee terminal of the input power converter 1 is connected to the negative electrode of the working power supply of the flyback switch type transducer 5; the Dr terminal of the current conversion state detector 2 is connected to the switch tube control electrode of the flyback switch type transducer 5; the positive feedback output end of the flyback switch type transducer 5 is connected to the Fe terminal of the current conversion state detector 2 The positive electrode of the output voltage of the flyback switch type transducer 5 is connected to the local ground and the detection input terminal of the current signal converter 4; the detection output terminal Io of the current signal converter 4 is connected to the anode of the LED lamp 6; the conversion output terminal of the current signal converter 4 is connected to the ReI terminal of the variable current state detector 2; the negative electrode Vo of the output voltage of the flyback switch type transducer 5 is connected to the cathode of the LED lamp 6 and the detection input terminal of the potential signal converter 3; the conversion output terminal of the potential signal converter 3 is connected to the ReV terminal of the variable current state detector 2.

[0013] The functions of the various components in the present invention are as follows: the input power converter 1 converts the mains electricity into pulsating direct current; the current conversion state detector 2 detects four input signals and adjusts the synthetic drive pulses it outputs in order to control the current conversion state of the system; the flyback switch type transducer 5 converts the pulsating direct current output by the input power converter 1 into direct current with corresponding power according to the critical strength of the positive synthetic drive pulse output by the current conversion state detector 2, and then drives the LED lamp 6 to emit light; the potential signal converter 3 detects the output potential of the flyback switch type transducer 5, and then converts it and negatively feeds it back to the current conversion state detector 2; the current signal converter 4 detects the output current of the flyback switch type transducer 5, and then converts it and negatively feeds it back to the current conversion state detector 2. In addition, the switch tube in the term "switch tube control electrode" mentioned in the previous paragraph is the abbreviation of a high-power semiconductor triode that is mainly used in a normal state of on or off. It has only one in the flyback switch type converter 5 and is an electronic switch that determines the current conversion state of the present invention; and the control electrode of the switch tube is either the base of a crystal triode or the gate of a field effect transistor...

[0014] The working principle of the present invention is as follows: the input power converter 1 rectifies and filters the unstable mains electricity and then outputs pulsating direct current, which not only provides working power for the flyback switch type transducer 5, but also sends a start signal to the St terminal; when the system is waiting for current conversion, the current conversion state detector 2 will output a driving pulse of sufficient intensity from the Dr terminal in a timely manner according to the start signal, and the driving pulse triggers the saturation of the switch tube in the flyback switch type transducer 5, and then the flyback switch type transducer 5 outputs a positive feedback pulse to the Fe terminal; the positive feedback pulse provides the current conversion state detector 2 with working power, and the current conversion state detector 2 also adjusts the positive synthesis driving pulse output from the Dr terminal according to the characteristics of the positive feedback pulse; at this point, the flyback switch type transducer 5 begins to enter the normal current conversion energy storage process, and thereafter, according to its own characteristics and state and the characteristics of the positive synthesis driving pulse, it starts to store magnetic energy on the one hand and determines the time for storing magnetic energy on the other hand;

[0015] When the energy storage process of the flyback switch type transducer 5 is completed, the potential of the positive feedback pulse (Fe) output by it changes dramatically from the peak value to the valley value, and the synthetic drive pulse output by the current conversion state detector 2 from the Dr terminal changes synchronously from a positive value to a negative value, which makes the flyback switch type transducer 5 start to enter the energy conversion process. Thereafter, according to its own characteristics and state as well as the characteristics of the negative synthetic drive pulse, on the one hand, it releases the magnetic energy just stored, and converts it into electrical energy and stores it again. This stored electrical energy does work on the LED lamp 6 in the form of DC potential (Vo), and on the other hand, determines the time of this energy conversion and the remaining time of this current conversion cycle.

[0016] When the transduction process of the flyback switching transducer 5 ends, it will enter a short inertia process. When the inertia process ends, the potential of the positive feedback pulse (Fe) output by it changes dramatically from the valley value to the peak value, and the synthetic drive pulse output from the Dr terminal of the variable current state controller 2 changes dramatically from the negative value to the positive value synchronously, which makes the flyback switching transducer 5 start to enter a short recovery process.

[0017] When the recovery process of the flyback switching transducer 5 is completed, that is, a complete current conversion cycle is completed, the system will automatically enter the energy storage process of the next current conversion cycle, ...; thus starting a new round of current conversion cycle of energy storage process → energy conversion process → inertia process → recovery process as described above; and so on, the flyback switching transducer 5 and the current conversion state detector 2 work closely together and interact with each other to perform switch-type DC conversion in the self-oscillation flyback mode.

[0018] During the current conversion process of the system, the potential signal converter 3 detects the output potential (Vo) of the flyback switch type transducer 5 in real time, and then converts the information and negatively feeds back to the ReV terminal of the current conversion state detector 2; the current signal converter 4 detects the output current (Io) of the flyback switch type transducer 5 in real time, and then converts the information and negatively feeds back to the ReI terminal of the current conversion state controller 2; the current conversion state controller 2 compares these two kinds of information with the user's expected output potential and current information set internally, and then appropriately adjusts the positive synthetic drive pulse output from the Dr terminal.

[0019] As the number of current conversion cycles increases, the absolute value of the output potential of the flyback switch type transducer 5 increases rapidly and the output current rises slowly. When the LED lamp 6 starts to glow, the automatic adjustment effect of the current conversion state detector 2 becomes increasingly greater, and the growth rate of the absolute value of the output potential of the flyback switch type transducer 5 becomes slower and slower or even decreases. If in several adjacent current conversion cycles, the potential information output by the potential signal converter 3 or the current information output by the current signal converter 4 are equal, it indicates that the system has entered the dynamic balance expected by the user, that is, the LED lamp 6 is emitting the luminous flux expected by the user.

[0020] Section 2 The current state detector 2 of the present invention can make the ratio of the rated output power to the minimum output power of the system exceed 30:1; its perfect internal structure consists of the following six modules: oscillation starter 7, drive strength calibrator 8, drive potential regulator 9, storage charge quencher 10, drive current regulator 11, switching process accelerator 12 (see Figure 2 ).

[0021] The connection method of each module in this component is: the St terminal of this component is connected to an input terminal of the oscillation starter 7; the other input terminal of the oscillation starter 7 is connected to the Fe terminal of this component; the output terminal of the oscillation starter 7 is connected to an input terminal of the driving strength calibrator 8; the other input terminal of the driving strength calibrator 8 is connected to the Fe terminal of this component; the output terminal of the driving strength calibrator 8 is connected to the Dr terminal of this component; the ReV terminal of this component is connected to the input terminal of the driving potential regulator 9; the output terminal of the driving potential regulator 9 is connected to the Dr terminal of this component; the ReI terminal of this component is connected to the input terminal of the driving current regulator 11; the output terminal of the driving current regulator 11 is connected to the Dr terminal of this component; the input terminal of the storage charge quick destroyer 10 is connected to the Dr terminal of this component; the output terminal of the storage charge quick destroyer 10 is connected to the Fe terminal of this component; one end of the switching process accelerator 12 is connected to the Fe terminal of this component; the other end of the switching process accelerator 12 is connected to the Dr terminal of this component.

[0022] The functions of each module in this component are as follows: an oscillator starter 7 replaces the upper bias resistor of the switch tube in the classical circuit, thereby reducing the switching loss and forward bias loss of the switch tube and eliminating the damage caused by load short circuit; a drive strength calibrator 8 outputs a drive pulse whose intensity is not affected by the input power converter 1 and accurately constrains the maximum current conversion power of the flyback switch type transducer 5; a switching process accelerator 12, which either shortens the disconnection time of the switch tube and reduces the switching loss, or shortens the connection time of the switch tube and reduces the minimum current conversion power of the flyback switch type transducer 5; a stored charge annihilator 10, which intelligently releases the redundant stored charge in the switch tube, thereby reducing the switching loss of the switch tube and reducing the reverse bias loss during the cut-off period of the switch tube; a drive potential regulator 9, which is used to adjust the critical potential of the positive synthesized drive pulse output from the Dr terminal of this component; a drive current regulator 11, which is used to adjust the critical current of the positive synthesized drive pulse output from the Dr terminal of this component.

[0023] The internal working principle of this component is: when the system is waiting for current conversion, the oscillation starter 7 delays the start signal of the St terminal of this component, and then triggers the drive strength calibrator 8 to output a drive pulse of fixed intensity; this drive pulse passes through the Dr terminal of this component, forcing the switch tube in the flyback switching transducer 5 to be deeply saturated; then the potential of the Fe terminal of this component is pulled by the positive feedback pulse output by the flyback switching transducer 5 and changes dramatically to a peak value; this positive feedback pulse is the working power supply of this component. On the one hand, it maintains the intensity of the drive pulse output from the Dr terminal of this component, and on the other hand, it clears the delay information of the start signal, so that the oscillation starter 7 no longer triggers the drive strength calibrator 8 - it does not interfere with the normal current conversion process of the system.

[0024] As mentioned above, the flyback switch transducer 5 closely cooperates with this component and interacts with it. Once the switch tube is triggered, the system will enter the normal current conversion process, and the positive feedback pulse (Fe) potential output by the flyback switch transducer 5 will automatically iterate between its peak value and valley value. To this excitation, the response of this component is as follows.

[0025] Whenever the potential of the positive feedback pulse (Fe) changes dramatically from the valley value to the peak value, the strong forward surge current passing through the switching process accelerator 12 is superimposed on the driving pulse output by the driving strength calibrator 8, and then shunted by the driving potential regulator 9 and the driving current regulator 11, and then output to the switch tube through the Dr terminal of this component; this synthetic driving pulse, due to the strong forward surge current component added by the switching, will accelerate the saturation conduction of the switch tube from the cut-off state and store sufficient charge. However, during the period when the potential of the positive feedback pulse (Fe) continues to be the peak value, the switching process accelerator 12 does not work, and the positive synthetic driving pulse output through the Dr terminal of this component does not have the strong forward surge current component, so as to accurately constrain the conversion power of the flyback switch-type transducer 5.

[0026] Whenever the potential of the positive feedback pulse (Fe) changes drastically from a peak value to a valley value, the strong reverse surge current of the switching process accelerator 12 is used to deduct the drive pulse output by the drive strength calibrator 8, and then superimposed with the current of the drive potential regulator 9 and the drive current regulator 11, and then input from the switch tube through the Dr terminal of this component; this synthetic drive pulse, due to the strong reverse surge current component added by the switching, will accelerate the release of the stored charge in the switch tube and accelerate the reduction of the critical saturation depth of the switch tube; and in this switching process, as long as the potential of the positive feedback pulse (Fe) is less than 0, the pulse current input from the switch tube through the Dr terminal of this component will be superimposed with the strong pulse current passing through the stored charge eliminator 10, further accelerating the release of the stored charge in the switch tube and further accelerating the reduction of the critical saturation depth of the switch tube. However, during the period when the potential of the positive feedback pulse (Fe) continues to be a valley value, the switching process accelerator 12, the drive strength calibrator 8, the drive potential regulator 9, and the drive current regulator 11 no longer function, and the pulse current passing through the stored charge destroyer 10 gradually becomes very small. This current is still input from the switch tube side through the Dr terminal of this component, so that the switch tube is in an excellent cut-off state.

[0027] During the current conversion process of the system, as long as the absolute value of the output potential (Vo) of the flyback switching transducer 5 is less than a certain value, the driving potential regulator 9 will not work; when the absolute value of the potential (Vo) is not less than a certain value, the driving potential regulator 9 will compare the output potential information from the ReV terminal of this component with the user's expected output potential information set inside it, and appropriately adjust the critical potential of the positive synthetic drive pulse output from the Dr terminal of this component, so as to achieve the purpose of changing the current conversion power of the flyback switching transducer 5 and making its output potential close to the expected value.

[0028] Similarly, as long as the output current (Io) of the flyback switching transducer 5 is less than a certain value, the driving current regulator 11 will not work; when the current (Io) is not less than a certain value, the driving current regulator 11 will compare the output current information from the ReI terminal of this component with the user's expected output current information set inside it, and appropriately adjust the critical current of the positive synthetic drive pulse output from the Dr terminal of this component, in order to achieve the purpose of changing the conversion power of the flyback switching transducer 5 to make its output current close to the expected value. DETAILED DESCRIPTION In order to realize products that meet the needs of people's home life according to the above-mentioned macro structure of the present invention, in practice, the specific structure of the circuit can be simplified as much as possible according to different working modes and technical indicators, so as to achieve the purpose of reducing costs and reducing debugging workload. The following is combined with a simplified embodiment of the steady current and voltage limiting working mode and the corresponding drawings to respectively describe the basic structure and working principle of each component in the present invention; in order to reduce the length of this specification, the specific technical details of the embodiment of the steady current and current limiting working mode of the present invention will not be repeated here.

[0029] In addition, in the drawings and in the process of describing the details of the technical solution as follows, the known technologies are appropriately simplified.

[0030] Section 3 The input power converter 1 component within the present invention uses classic power conversion technology in this embodiment to convert unstable AC power into direct current that can pulsate between 180V and 365V. The positive pole of the power supply is output from the Ec terminal, and the negative pole of the power supply is output from the Ee terminal. It is the working power supply of the flyback switching transducer 5 component, and its internal structure and working principle are not described in detail here.

[0031] Section 4 The LED lamp 6 components of the present invention, in this embodiment, refer to the classic LED lighting lamp, which is internally connected by a group of ordinary LED lamp beads with the same electrical characteristics. The simplified diagram of its internal circuit can be referred to Figure 3 ; The light-emitting principle of LED will not be described here.

[0032] Section 5 The potential signal converter 3 of the present invention has only a voltage stabilizing diode 33 (see FIG. Figure 3 The connection method is as follows: the anode of the voltage-stabilizing diode 33 is used as the detection input terminal of the component, connected to the negative electrode Vo of the output voltage of the flyback switch type transducer 5 and the cathode of the LED lamp 6; the cathode of the voltage-stabilizing diode 33 is used as the conversion output terminal of the component, connected to the ReV terminal of the current conversion state detector 2.

[0033] The voltage-stabilizing diode 33 here acts as a subtractor with a threshold and a gain of 1. In this embodiment, a high-precision circuit such as an operational amplifier is not used because this can also make the error of the maximum operating potential of the LED lamp 6 not exceed 5%, and also to highlight the key points of the present invention and reduce the length of the description.

[0034] The internal working principle of this component is: when the absolute value of the output potential (Vo) of the flyback switch type transducer 5 is less than the breakdown voltage of the Zener diode 33, there is no breakdown current in the Zener diode 33, and therefore it will not affect the working state of the converter state detector 2; and when the absolute value of the output potential (Vo) of the flyback switch type transducer 5 is not less than the breakdown voltage of the Zener diode 33, the Zener diode 33 will generate a corresponding breakdown current, the magnitude of which determines the potential of the ReV terminal; this will prompt the converter state controller 2 to adjust the critical potential of the positive synthetic drive pulse output from its Dr terminal accordingly.

[0035] Section 6 The current signal converter 4 of the present invention has only a variable resistor 42 (see Figure 3 ). The connection method is: one terminal of the variable resistor 42 is used as the detection input terminal of this component, connected to the positive electrode of the output voltage of the flyback switch type transducer 5, that is, the local ground; the other terminal of the variable resistor 42 is used as the detection output terminal Io of this component, connected to the anode of the LED lamp 6 and the ReV terminal of the variable current state detector 2 (this is a simplified embodiment, so the Io terminal is directly connected to the ReI terminal).

[0036] The variable resistor 42 directly feeds back the output current signal of the flyback switch type transducer 5 to the current conversion state detector 2 in the form of potential; no high-precision circuits such as operational amplifiers are added here because this can also make the error of the working current of the LED lamp 6 not more than 5%, and also to highlight the key points of the present invention and reduce the length of the narrative.

[0037] The internal working principle of this component is: when the output current of the flyback switch type transducer 5 is less than a certain value, the potential (Io) output by the variable resistor 42 will not affect the working state of the current conversion state detector 2; and when the output current of the flyback switch type transducer 5 is not less than a certain value, the potential output by the variable resistor 42 will prompt the current conversion state controller 2 to adjust the critical current of the positive synthetic drive pulse output from its Dr terminal accordingly.

[0038] Section 7 The flyback switch type transducer 5 components of the present invention are composed of diodes 34, 35, 41, NPN transistor 36, resistor 37, electrolytic capacitor 38, pulse transformer primary coil 39, pulse transformer secondary coil 40 and other components in this embodiment (see Figure 3 ).

[0039] The connection method of each component in this component is: the Ec terminal of the input power converter 1 is connected to the positive electrode of the working power supply of this component, that is, the collector of the transistor 36 and the cathode of the diode 41; the Dr terminal of the current state detector 2 is connected to the switch tube control electrode of this component, that is, the base of the transistor 36 and the cathode of the diode 34; the emitter of the transistor 36 is connected to one end of the resistor 37; the other end of the resistor 37 is connected to the anode of the diode 34 and the anode of the diode 41 and connected to the local ground; the positive electrode of the capacitor 38, as the positive electrode of the output voltage of this component, is connected to the local ground; the anode of the LED lamp 6 is indirectly connected to the detection end of the current signal converter 4 The local ground (because the impedance of the current signal converter 4 is extremely small); the negative electrode of the capacitor 38, as the negative electrode Vo of the output voltage of this component, is connected to the same-name end (the side with the symbol "*") of the primary coil 39 and the cathode of the LED lamp 6 and the detection input end of the potential signal converter 3; the Ee terminal of the input power converter 1 is connected to the negative electrode of the working power supply of this component, that is, the non-same-name end of the primary coil 39 and the anode of the diode 35; the cathode of the diode 35 is connected to the non-same-name end of the secondary coil 40 and connected to the local ground; the same-name end (the side with the symbol "*") of the secondary coil 40, as the positive feedback output end of this component, is connected to the Fe terminal of the inverter state detector 2.

[0040] The functions of the components in this part are as follows: diode 34 is used to protect the emitter junction of transistor 36 from reverse breakdown; transistor 36 acts as a switch tube, mainly to make the primary coil 39 forwardly excited and the LED lamp 6 do work; resistor 37 is used to reduce the impact of the parameter difference of transistor 36 on the system technical indicators; secondary coil 40 feeds back the working state of the primary coil 39 to the inverter state detector 2 in the form of pulse voltage; diode 35 acts as a main freewheeling tube, mainly used to transfer the magnetic energy stored in the forward excitation of the primary coil 39 to capacitor 38 and LED lamp 6; capacitor 38 is used to store electrical energy and drive the LED lamp 6 to emit light; diode 41 acts as an auxiliary freewheeling tube, mainly used to feed back the magnetic energy stored in the reverse excitation of the primary coil 39 to the input power converter 1.

[0041] The working principle of this component is as follows: when the system is waiting for current conversion, the current conversion state detector 2 outputs a driving pulse of sufficient intensity from the Dr terminal in a timely manner according to the start signal of the St terminal, which triggers the base of the switch tube - transistor 36 to initially appear current, thereby changing the transistor 36 from the cut-off state to the deep saturation state; then the DC current from the input power converter 1 flows into the collector and out of the emitter of the transistor 36, and then passes through the resistor 37, and then passes through the capacitor 38 and the LED lamp 6 respectively to positively excite the primary coil 39, that is, the primary coil 39 begins to enter the positive excitation period (energy storage process); during this period, the positive feedback pulse (Fe) output by the secondary coil 40 rises in potential and remains at a peak value, the Dr terminal continues to output driving pulses, the positive excitation current of the primary coil 39 increases linearly, the stored magnetic energy increases sharply, and the saturation depth of the transistor 36 becomes shallower and shallower.

[0042] When the transistor 36 retreats from the saturation state to the deep critical saturation state, the component begins to enter the disconnection switching period (circuit breaking process) of the switch tube; during this period, the voltage between the collector and the emitter of the transistor 36 begins to increase significantly, so the positive feedback pulse (Fe) potential output by the secondary coil 40 begins to decrease significantly, which causes the synthetic drive pulse intensity output by the Dr terminal to decrease significantly, thereby causing the critical saturation depth of the transistor 36 to decrease significantly, that is, the base current and the forward excitation current between the collector and the emitter through the transistor 36 also decrease significantly. Since the inductor current cannot change suddenly, the current through the diode 35 begins to increase significantly; and because the diode 35 intervenes At the end of this forward excitation, the positive feedback pulse potential output by the secondary coil 40 is further reduced, the synthetic drive pulse intensity output by the Dr terminal is further reduced, the critical saturation depth of the transistor 36 is further reduced, the forward excitation current passing through its collector-emitter is further reduced, but the current of the diode 35 is further increased; this is a short and strong positive feedback switch tube disconnection process, the result of which is: the positive feedback pulse (Fe) potential output by the secondary coil 40 changes dramatically from the peak value to the valley value, the synthetic drive pulse output by the inverter state detector 2 from its Dr terminal changes synchronously from the positive value to the negative value, the diode 35 is turned on, and the transistor 36 is basically cut off.

[0043] When the transistor 36 is about to be cut off, the primary coil 39 begins to enter the forward demagnetization period (energy conversion process); during this period, the forward excitation current of the primary coil 39 decreases linearly, and its stored magnetic energy passes through the diode 35 to do work on the LED lamp 6 and charge the capacitor 38 respectively; at the same time, the positive feedback pulse (Fe) potential output by the secondary coil 40 continues to be a valley value, and the synthetic drive pulse output by the Dr terminal continues to be a negative value, so the transistor 36 is in the cut-off state.

[0044] When the forward excitation current of the primary coil 39 is reduced to zero, because the inductor current and the diode terminal voltage cannot change suddenly, the electric energy stored in the capacitor 38, in addition to doing work on the LED lamp 6, also reversely excites the primary coil 39 through the reverse current of the diode 35, that is, the primary coil 39 begins to enter the reverse excitation period (inertia process); during this period, the absolute value of the reverse excitation current of the primary coil 39 also increases linearly, the terminal voltage of the capacitor 38 decreases slightly, the charge stored in the diode 35 becomes less and less, and the positive feedback pulse (Fe) potential output by the secondary coil 40 continues to be a valley value.

[0045] When the reverse excitation time of the primary coil 39 reaches the inherent storage time of the diode 35, this component begins to enter the switch-on switching period (path process) of the switch tube; during this period, the absolute value of the reverse excitation current through the diode 35 begins to decrease significantly, and the absolute value of the voltage at the diode 35 begins to increase significantly, so the positive feedback pulse (Fe) potential output by the secondary coil 40 begins to rise significantly, which causes the synthetic drive pulse intensity output by the Dr terminal to rise significantly, and then current appears in the base of the transistor 36, which in turn changes the transistor 36 from the cut-off state to the saturation state; because the inductor current cannot change suddenly, the transistor 36 at this time is reversely conducted like an inverted common-emitter switch, and the reverse excitation current reduced by the diode 35 flows from the emitter of the transistor 36 through the resistor 37. , the collector flows out and is fed back to the input power converter 1; because the input power converter 1 intervenes in the final stage of this reverse excitation, the absolute value of the voltage at the diode 35 terminal is further increased, the positive feedback pulse (Fe) potential output by the secondary coil 40 is further increased, the synthetic drive pulse intensity output by the Dr terminal is further increased, the absolute value of the reverse excitation current through the diode 35 is further reduced, and the absolute value of the reverse current between the collector and the emitter of the transistor 36 is further increased; this is a short positive feedback switch tube connection process, and the result is: the positive feedback pulse (Fe) potential output by the secondary coil 40 changes sharply from the valley value to the peak value, the synthetic drive pulse output by the current conversion state detector 2 from its Dr terminal changes sharply from the negative value to the positive value synchronously, the diode 35 is basically cut off, and the transistor 36 is reversely conducted. On the other hand, when the positive feedback pulse (Fe) potential begins to rise from the valley value to the peak value, the reverse bias voltage of the collector junction of the transistor 36 is not less than tens of volts, so the diode 34 is used to clamp the voltage of the emitter junction of the transistor 36 in the safe area.

[0046] When the diode 35 is about to be cut off, the primary coil 39 begins to enter the reverse demagnetization period (recovery process); during this period, the absolute value of the reverse excitation current in the primary coil 39 decreases linearly, and its stored magnetic energy first flows back to the input power converter 1 through the capacitor 38 and then through the resistor 37 and the transistor 36 branch. The terminal voltage of the capacitor 38 also decreases slightly, and the positive feedback pulse (Fe) potential output by the secondary coil 40 continues to be the peak value. The diode 35 is cut off. Although the diode 41 is turned on with a delay, most of the magnetic energy stored in the reverse excitation of the primary coil 39 is fed back to the input power converter 1.

[0047] When the absolute value of the reverse excitation current in the primary coil 39 drops to zero, a complete current conversion cycle ends. At this time, the positive feedback pulse (Fe) potential output by the secondary coil 40 has reached a peak value, the Dr terminal of the current conversion state detector 2 has also output a positive synthetic drive pulse of appropriate strength, the transistor 36 is in a reverse conduction state, and the diode 41 is in a forward conduction state. Because the inductor current and the diode terminal voltage cannot change suddenly, the DC current from the input power converter 1 passes through the transistor 36 and the resistor 37 branch and the diode 41 respectively. The primary coil 39 is then forwardly excited through the capacitor 38 and the LED lamp 6, that is, the primary coil 39 begins to enter the forward excitation period again; during this period, the forward excitation current of the primary coil 39 still increases linearly, so the transistor 36 quickly changes from the reverse conduction state to the forward deep saturation state, and the diode 41 is automatically turned off due to its extremely short reverse recovery time (this has little effect on the forward excitation state of the primary coil 39); thereafter, the excitation state and process of the primary coil 39 are exactly the same as the same stage mentioned above, and will not be repeated here.

[0048] To sum up: this component closely cooperates and interacts with the current conversion state detector 2. Once the switch tube - the transistor 36 is triggered, the primary coil 39 of the pulse transformer will be in the forward excitation period, and its state will automatically reciprocate according to the above-mentioned six working stages and their sequence; thereby, the electric energy transmitted by the input power converter 1 is continuously converted to the electrolytic capacitor 38 and the LED lamp 6.

[0049] The current conversion power of this component, after the circuit parameters of the system are determined, depends only on the critical intensity of the positive synthetic drive pulse output from the Dr terminal of the current conversion state detector 2 during the positive excitation period.

[0050] During the experiment, it was observed that the excitation current through the primary coil 39 either rises linearly or falls linearly, and the current waveform is mainly composed of two straight line segments. Since the critical intensity of the positive synthetic drive pulse output from the Dr terminal determines the maximum critical saturation depth of the transistor 36, this indirectly determines the maximum forward excitation current of the primary coil 39 and the required forward excitation time, and the maximum forward excitation current determines the forward demagnetization time and reverse excitation time of the primary coil 39, and because the maximum absolute value of the reverse excitation current determines the reverse demagnetization time of the primary coil 39; therefore, the current conversion cycle of this component has been indirectly determined, and the above conclusion can be obtained based on the theory that the magnetic energy stored in the inductor is proportional to the square of its excitation current.

[0051] Section 8 The oscillation starter 7 module of the present invention is composed of resistors 13, 17, capacitors 14, 18, a one-way trigger diode 15, a one-way thyristor 16, a diode 19 and other components in this embodiment (see Figure 4 ).

[0052] The connection method of each component in this module is: the St terminal of the variable current state detector 2 is connected to one end of the resistor 13; the other end of the resistor 13, namely the node N14, is connected to one end of the capacitor 14 and the anode of the unidirectional trigger diode 15 and the anode of the unidirectional thyristor 16; the other end of the capacitor 14 is connected to the local ground; the cathode of the unidirectional trigger diode 15 is connected to an input end of the drive strength calibrator 8, namely the node N21; the cathode of the unidirectional thyristor 16 is connected to the anode of the diode 19 and the local ground; the control electrode of the unidirectional thyristor 16 is connected to one end of the resistor 17; the other end of the resistor 17 is connected to one end of the capacitor 18 and the cathode of the diode 19; the other end of the capacitor 18 is connected to the Fe terminal of the variable current state detector 2.

[0053] This module is a synchronizable self-excited multivibrator, and the functions of the components therein are as follows: the resistor 13 and the capacitor 14 cooperate to be used for timing to delay the start signal; the unidirectional trigger diode 15 is used to trigger the drive strength calibrator 8 to start outputting the drive pulse; the unidirectional thyristor 16 is used to clear the redundant charge in the capacitor 14; the resistor 17 is used to constrain the maximum current of the control electrode of the unidirectional thyristor 16; the capacitor 18 and the diode 19 cooperate to detect the moment when the positive feedback pulse (Fe) potential starts to rise from the valley value.

[0054] The working principle inside this module is: when the system is waiting for current conversion, resistor 13 inputs current from the St terminal to charge capacitor 14; thereafter, the potential of node N14 gradually rises with the passage of time, and when the potential of node N14 exceeds the breakdown voltage of the unidirectional trigger diode 15, the unidirectional trigger diode 15 is turned on and transmits the electric energy stored in capacitor 14 to the drive strength calibrator 8, so that it outputs a drive pulse of fixed intensity; then the potential of the Fe terminal is pulled and rises by the positive feedback pulse output by the flyback switch type transducer 5, and since the voltage at the capacitor terminal cannot change suddenly, this causes the surge current that suddenly appears in capacitor 18 to trigger the unidirectional thyristor 16 to turn on through resistor 17; after the unidirectional thyristor 16 is turned on, the redundant charge in capacitor 14 is released, so that the unidirectional trigger diode 15 is no longer turned on - so as not to interfere with the normal current conversion process of the system.

[0055] Section 9 The drive strength calibrator 8 module of the present invention is composed of a diode 20, an N-channel junction field effect transistor 21, a resistor 22 and other components in this embodiment (see Figure 4 ). The connection method of each component in this module is: the Fe terminal of the variable current state detector 2 is connected to the anode of the diode 20; the cathode of the diode 20, that is, the node N21, is connected to the drain of the field effect tube 21 and the output end of the oscillation starter 7 module; the source of the field effect tube 21 is connected to one end of the resistor 22; the other end of the resistor 22 is connected to the gate of the field effect tube 21 and the Dr terminal of the variable current state detector 2.

[0056] This module is a variable constant current device, in which the functions of each component are as follows: diode 20 is used to limit this module to work only when the potential of Fe terminal is greater than 0; field effect transistor 21 is used to prevent the influence of system working power supply fluctuation on the output current of this module; resistor 22 is used to adjust the size of the output current of this module and constrain the maximum current conversion power of the system.

[0057] The working principle inside this module is: as long as the oscillation starter 7 module outputs a trigger pulse, or the peak value of the Fe terminal potential forces the diode 20 to turn on, the potential of the node N21 will increase, and this will cause the resistor 22 to output a constant current of the expected intensity due to the constant current characteristics of the field effect transistor 21; once the oscillation starter 7 does not work and the potential of the Fe terminal is not greater than zero, this module will not output current.

[0058] Section 10 The switching process accelerator 12 module in the present invention is composed of a capacitor 31 and a resistor 32 in this embodiment (see Figure 4 The connection method of these two components is: the Fe terminal of the variable current state detector 2 is connected to one end of the capacitor 31; the other end of the capacitor 31 is connected to one end of the resistor 32; the other end of the resistor 32 is connected to the Dr terminal of the variable current state detector 2.

[0059] This module is a pulse edge detector, and only passes surge current during switching. The functions of the components are: capacitor 31, which mainly determines the intensity of the surge current; resistor 32, which mainly determines the duration of the surge current.

[0060] The working principle inside this module is: during the period when the potential of the Fe terminal changes drastically from the valley value to the peak value, because the potential of the Dr terminal does not change much, that is, the rate of change of the voltage at the capacitor 31 is too large, a strong positive surge current will pass through this module; this current is synthesized with other multiple pulses in the converter state detector 2 and output from its Dr terminal, in order to strongly shorten the switching process of the switch tube and reduce the minimum converter power of the system; and during the period when the potential of the Fe terminal continues to be the peak value, there is no current in this module, so it will not affect the critical strength of the positive synthesized drive pulse output by the Dr terminal.

[0061] Similarly, during the period when the potential of the Fe terminal changes drastically from the peak value to the valley value, a strong reverse surge current will pass through this module; this current is synthesized with other multiple pulses in the converter state detector 2 and input from its Dr terminal, in order to greatly shorten the disconnection and switching process of the switch tube and reduce the switching loss; and during the period when the potential of the Fe terminal continues to be the valley value, there is no current in this module, so it will not affect the characteristics of the negative synthetic drive pulse output by the Dr terminal.

[0062] Section 11 The stored charge destroyer 10 module of the present invention is composed of diodes 24, 26, a constant current diode 25, a PNP transistor 27 and other components in this embodiment (see Figure 4 ).

[0063] The connection method of each component in this module is: the Fe terminal of the variable current state detector 2 is connected to the cathode of the diode 26; the anode of the diode 26 is connected to the cathode of the constant current diode 25 and the collector of the transistor 27; the anode of the constant current diode 25 is connected to the base of the transistor 27 and the cathode of the diode 24; the anode of the diode 24 is connected to the local ground; the emitter of the transistor 27 is connected to the Dr terminal of the variable current state detector 2.

[0064] This module is an intelligent clamp, and the functions of its components are as follows: diode 26 is used to limit this module to work only when the potential of the Fe terminal is less than 0; diode 24 provides a reference potential to determine whether the potential of the Dr terminal is slightly less than zero; constant current diode 25 is used to limit the maximum current of the emitter of transistor 27 or the conduction voltage of diode 24; transistor 27 generates a corresponding emitter current according to the voltage difference between this reference potential and the potential of the Dr terminal.

[0065] The working principle of this module is: when the potential of the Fe terminal is ≥ 0, the module does not work because the diode 26 is turned off; when the potential of the Fe terminal is < 0, the module starts to work because the diode 26 is turned on, and when the potential of the Dr terminal is very high, the diode 24 is turned off and the current of the constant current diode 25 all passes through the base of the transistor 27, so that the strong emitter current of the transistor 27 is synthesized with other multi-channel pulses in the variable current state detector 2 and input from the switch tube through the Dr terminal, so as to strongly shrink The disconnection and switching process of the short switch tube is shortened, and the switching loss is reduced; when the potential of the Dr terminal drops to about 300 mV, the diode 24 begins to show a forward current, and the base current and emitter current of the transistor 27 are reduced accordingly, but the stored charge in the switch tube continues to be released through the Dr terminal; when the potential of the Dr terminal is less than zero, it indicates that the stored charge in the switch tube is no longer redundant. At this time, the diode 24 is in the on state. Because the voltage of the emitter junction of the transistor 27 is very small, its emitter current is very small, which will reduce the reverse bias loss of the switch tube.

[0066] Section 12 The driving potential regulator 9 module in the present invention is only composed of a PNP type triode 23 in this embodiment (see Figure 4 ). The connection method is: the ReV terminal of the current state detector 2 is connected to the base of the transistor 23; the emitter of the transistor 23 is connected to the Dr terminal of the current state detector 2; the collector of the transistor 23 is connected to the local ground.

[0067] This module is a high-speed clamp and a typical common-collector circuit with all the advantages of an emitter follower.

[0068] The working principle inside this module is: when the system is in dynamic equilibrium and the potential of the Fe terminal is at a peak value, the potential of the ReV terminal is the expected value, the voltage of the emitter junction of the transistor 23 is also the expected value, and the critical potential of the positive synthetic drive pulse output from the Dr terminal is also the expected value; if the potential of the ReV terminal is higher than its expected value by Δ, the emitter junction voltage of the transistor 23 will be slightly lower than its expected value, which will cause the emitter current of the transistor 23 to drop significantly and its shunt effect to drop significantly, so the critical potential of the positive synthetic drive pulse output from the Dr terminal is also higher than its expected value by Δ, which can increase the system's current conversion power; if the potential of the ReV terminal is lower than its expected value by Δ, the emitter junction voltage of the transistor 23 will be slightly higher than its expected value, which will cause the emitter current of the transistor 23 to increase significantly and the shunt effect to increase significantly, so the critical potential of the positive synthetic drive pulse output from the Dr terminal is also lower than its expected value by Δ, which can reduce the system's current conversion power.

[0069] When the potential of the Fe terminal is at a valley value, the module does not work. Even when the system's current conversion power is very small, the two PN junctions of the transistor 23 will not be in a saturated state, so the regulation response speed of the module is very high.

[0070] Section 13 The drive current regulator 11 module in the present invention is composed of a PNP transistor 28, an NPN transistor 30 and a Schottky diode 29 in this embodiment (see Figure 4 ). The connection method of these three components is: the Dr terminal of the variable current state detector 2 is connected to the emitter of the transistor 28; the base of the transistor 28 is connected to the cathode of the diode 29 and the collector of the transistor 30; the collector of the transistor 28 is connected to the anode of the diode 29 and the base of the transistor 30 and connected to the local ground; the emitter of the transistor 30 is connected to the ReI terminal of the variable current state detector 2.

[0071] This module is a fast shunt, which is constructed into a common base circuit with anti-saturation opposite polarity Darlington tubes, in which the functions of each component are as follows: transistor 28 is used to prevent the response speed of the driving current regulation from being significantly slowed down and to prevent the output power range of the system from being significantly reduced; transistor 30 is used to convert the current regulation signal in the form of potential into the form of current; Schottky diode 29 is mainly used to prevent the transistor 30 from entering a deep saturation state.

[0072] The working principle of this module is: when the system is in dynamic equilibrium and the potential of the Fe terminal is at its peak, the potential of the ReI terminal is the expected value, the emitter current of transistors 28 and 30 is also the expected value, and the critical current of the positive synthetic drive pulse output from the Dr terminal is also the expected value; if the potential of the ReI terminal is higher than its expected value by Δ, that is, the emitter junction voltage of transistor 30 is lower than its expected value by Δ, this will cause the emitter current of transistor 30 and the base current of transistor 28 to be significantly reduced than their expected values, thereby causing the emitter of transistor 28 to have a shunt effect. It decreases sharply, so the critical current of the positive synthetic drive pulse output from the Dr terminal will be much larger than its expected value, which can increase the system's current conversion power; if the potential of the ReI terminal is lower than its expected value by Δ, that is, the emitter junction voltage of the transistor 30 is higher than its expected value by Δ, this will cause the emitter current of the transistor 30 and the base current of the transistor 28 to increase significantly than their expected values, thereby causing the shunting effect of the emitter of the transistor 28 to increase sharply. Therefore, the critical current of the positive synthetic drive pulse output from the Dr terminal will be much smaller than its expected value, which can reduce the system's current conversion power.

[0073] When the potential of the Fe terminal is at a valley value, this module does not work. When the output power of the system is small, the Schottky diode 29 starts to prevent the transistor 30 from being in a deep saturation state, so the regulation response speed of this module is relatively high.

[0074] Advantages of the invention: By using the LED light intensity continuously variable stabilizer, the ratio of the rated power to the minimum power of the LED lamp 6 can be made greater than 30, and people can continuously adjust the luminous intensity of the LED lamp 6 within this wide range according to the required illumination of the living environment. This can reduce the types of indoor lighting fixtures and simplify lighting circuits.

[0075] The present invention has a high power utilization rate. To adapt to the high input voltage, low working voltage of LED lighting and its usage habits, the flyback switch type transducer 5 component adopted by the present invention encompasses the main advantages of the classic single-tube self-excited oscillation flyback switch type DC regulated power supply. This component does not require an independent damping circuit, and also uses an auxiliary freewheeling tube (diode 41) to assist the switch tube (transistor 36) for reverse demagnetization, which can not only recover more redundant magnetic energy, but also make the system more stable and the current conversion wave more pure.

[0076] In the converter state detector 2 component that closely cooperates with the flyback switch type transducer 5 component, the four modules of the self-excited oscillation starter 7, the drive strength calibrator 8, the switching process accelerator 12, and the stored charge destroyer 10 have made unique contributions to reducing system power consumption.

[0077] The above-mentioned various measures for reducing system power consumption not only make the power utilization rate of the present invention higher than that of the classical circuit, but also reduce unnecessary heat generation - the temperature rise of the present invention is smaller.

[0078] The output power variation range of the present invention is very wide. The drive strength calibrator 8 module adopts the advanced control technology, which is the first factor that the ratio of the system rated output power to the minimum output power is greater than 30; in addition to the basic performance, this module also reduces the unnecessary power consumption when outputting the drive pulse. The drive potential regulator 9 module adopts the negative feedback control technology with ultra-high response speed. Even when the system outputs the minimum power, it has a high-precision automatic adjustment capability, which is the second factor that the ratio of the system rated output power to the minimum output power is greater than 30; experiments show that it is also very effective to directly stabilize the working current of the LED lamp 6. The switching process accelerator 12 module makes the switch tube enter the reverse conduction state, which is the third factor that the ratio of the system rated output power to the minimum output power is greater than 30.

[0079] In addition, the working status of the LED lamp 6 is "directly" fed back to the driving potential regulator 9 module and the driving current regulator 11 module without using low-speed devices such as optocouplers as intermediaries, which is the fourth factor that the ratio of the system rated output power to the minimum output power is greater than 30.

[0080] The present invention has the ability to resist load short circuit. In daily life, the load (LED lamp 6) short circuit phenomenon is inevitable. Therefore, the present invention adopts the self-excited oscillation starter 7 module to ensure that when the load is short-circuited, the system can safely and dynamically wait for the fault to be eliminated.

[0081] The best way to implement the invention is to use integrated circuit technology to organically combine the self-excited oscillation starter 7 module, drive strength calibrator 8 module, drive potential regulator 9 module, drive current regulator 11 module, charge storage depletor 10 module, and even the switching process accelerator 12 module in the present invention except the resistor 13 and the capacitor 14 into a substrate to make an integrated circuit suitable for a single-tube self-excited oscillation flyback switching type DC stable power supply - a current conversion state detector.

[0082] As described above, the present invention can have fewer visual elements, a smaller volume, a lower cost, better consistency of technical indicators, and be easier to design, produce and debug.

Claims

1. An LED light intensity continuously variable stabilizer, comprising an input power converter (1), an LED lamp (6), a potential signal converter (3), and a current signal converter (4); characterized in that: The current conversion state detector (2) detects the output potential of the input power converter (1), the current conversion state signal fed back by the flyback switch type transducer (5), the output potential signal of the flyback switch type transducer (5) fed back by the potential signal converter (3), and the output current signal of the flyback switch type transducer (5) fed back by the current signal converter (4), and adjusts the output drive pulse to control the current conversion state of the flyback switch type transducer (5); the flyback switch type transducer (5) converts the pulsating direct current output by the input power converter (1) into stable direct current according to the drive pulse output by the current conversion state detector (2), and then drives the LED lamp (6) to emit light; and the mains is connected to the input end of the input power converter (1); the E c The positive feedback output terminal of the flyback switch type transducer (5) is connected to the Fe terminal of the current conversion state detector (2); the positive electrode of the output voltage of the flyback switch type transducer (5) is connected to the positive electrode of the working power supply of the flyback switch type transducer (5) and the St terminal of the current conversion state detector (2); the Ee terminal of the input power converter (1) is connected to the negative electrode of the working power supply of the flyback switch type transducer (5); the Dr terminal of the current conversion state detector (2) is connected to the switch tube control electrode of the flyback switch type transducer (5); the positive feedback output terminal of the flyback switch type transducer (5) is connected to the Fe terminal of the current conversion state detector (2); the positive electrode of the output voltage of the flyback switch type transducer (5) is connected to the local ground and the detection input end of the current signal converter (4); the detection output end Io of the current signal converter (4) is connected to the anode of the LED lamp (6); the conversion output end of the current signal converter (4) is connected to the ReI terminal of the variable current state detector (2); the negative pole Vo of the output voltage of the flyback switch type transducer (5) is connected to the cathode of the LED lamp (6) and the detection input end of the potential signal converter (3); the conversion output end of the potential signal converter (3) is connected to the ReV terminal of the variable current state detector (2).

2. The variable current state detector (2) component of the LED light intensity continuously variable stabilizer as claimed in claim 1 is characterized by: An oscillator starter (7) that replaces the forward bias circuit of the switch tube to reduce its switching loss and eliminate the damage caused by the short circuit of the system load; a drive strength calibrator (8) that outputs a driving pulse and is not affected by the input power converter (1) to constrain the maximum current conversion power of the flyback switch type transducer (5); a switching process accelerator (12) that shortens the switching time of the switch tube and reduces the minimum current conversion power of the flyback switch type transducer (5); a stored charge annihilator (10) that intelligently releases the redundant charge in the switch tube to reduce its switching loss; a driving potential regulator (9) that regulates the maximum potential of the switch tube driving pulse; and a driving current regulator (11) that regulates the maximum current of the switch tube driving pulse; and the St terminal of the current conversion state detector (2) is connected to an input terminal of the oscillator starter (7); the other input terminal of the oscillator starter (7) is connected to the Fe terminal of the current conversion state detector (2); the output terminal of the oscillator starter (7) is connected to an input terminal of the drive strength calibrator (8); the other input terminal of the drive strength calibrator (8) is connected to the input terminal of the drive strength calibrator (8); An input end is connected to the Fe terminal of the variable current state detector (2); the output end of the drive strength calibrator (8) is connected to the Dr terminal of the variable current state detector (2); the ReV terminal of the variable current state detector (2) is connected to the input end of the drive potential regulator (9); the output end of the drive potential regulator (9) is connected to the Dr terminal of the variable current state detector (2); the ReI terminal of the variable current state detector (2) is connected to the input end of the drive current regulator (11); the drive current regulator The output end of the regulator (11) is connected to the Dr terminal of the current conversion state detector (2); the input end of the charge storage and rapid elimination device (10) is connected to the Dr terminal of the current conversion state detector (2); the output end of the charge storage and rapid elimination device (10) is connected to the Fe terminal of the current conversion state detector (2); one end of the switching process accelerator (12) is connected to the Fe terminal of the current conversion state detector (2); and the other end of the switching process accelerator (12) is connected to the Dr terminal of the current conversion state detector (2).

3. The flyback switch type transducer (5) component of the LED light intensity continuously variable stabilizer as described in claim 1 comprises diodes (34), (35), (41), NPN transistors (36), resistors (37), electrolytic capacitors (38), pulse transformer primary coils (39), and pulse transformer secondary coils (40), wherein the transistor (36) acts as a switch tube to forward excite the primary coil (39) and charge the capacitor (38), the electric energy in the capacitor (38) drives the LED lamp (6) to emit light, and the diode (35) acts as a main freewheeling tube to charge the primary coil ( The forward excitation stored energy in the transistor (39) is transferred to the capacitor (38), and the diode (34) protects the emitter junction of the transistor (36) from reverse breakdown; the flyback switch type transducer (5) is characterized in that: the resistor (37) can reduce the influence of the parameter difference of the transistor (36) on the system technical indicators, the series switch self-excited oscillation structure with smaller output voltage ripple, the electrolytic capacitor (38) is connected between the transistor (36) and the primary coil (39), and the withstand voltage requirement of the device is lower; and the Ec terminal of the input power converter (1) is connected to the collector of the transistor (36) and the diode ( The cathode of the current state detector (2) is connected to the base of the transistor (36) and the cathode of the diode (34); the emitter of the transistor (36) is connected to one end of the resistor (37); the other end of the resistor (37) is connected to the anode of the diode (34) and the anode of the diode (41) and connected to the local ground; the positive electrode of the capacitor (38) is connected to the local ground as the positive electrode of the output voltage of the flyback switch type transducer (5); the anode of the LED lamp (6) is indirectly connected to the local ground through the detection end of the current signal converter (4); the negative electrode of the capacitor (38) is connected to the local ground as The negative electrode Vo of the output voltage of the flyback switch type transducer (5) is connected to the same-name end of the primary coil (39), the cathode of the LED lamp (6) and the detection input end of the potential signal converter (3); the Ee terminal of the input power converter (1) is connected to the non-same-name end of the primary coil (39) and the anode of the diode (35); the cathode of the diode (35) is connected to the non-same-name end of the secondary coil (40) and is connected to the local ground; the same-name end of the secondary coil (40) is used as the positive feedback output end of the flyback switch type transducer (5) and is connected to the Fe terminal of the current conversion state detector (2).

4. The oscillation starter (7) module of the variable current state detector (2) component of the LED light intensity continuously variable stabilizer as described in claim 1 or 2 comprises resistors (13), (17), capacitors (14), (18), a unidirectional trigger diode (15), a unidirectional thyristor (16), and a diode (19); the oscillation starter (7) is characterized in that: it is self-excited and can be synchronized, and the bias circuit of the transistor (36) is replaced by the oscillation starter (7), which can not only reduce the loss of the transistor (36), but also prevent the transistor (36) from being burned when the load is short-circuited; wherein, The resistor (13) and the capacitor (14) are used for timing to delay the start signal, the unidirectional trigger diode (15) timely triggers the drive strength calibrator (8) to output the drive pulse, the unidirectional thyristor (16) timely clears the redundant charge in the capacitor (14), the resistor (17) limits the maximum current of the control electrode of the unidirectional thyristor (16), the capacitor (18) and the diode (19) synchronize the oscillation starter (7) at the moment when the positive feedback pulse potential starts to rise from the valley value; and the St terminal of the variable current state detector (2) is connected to one end of the resistor (13); the other end of the resistor (13), i.e., the node N14, is connected to the One end of the capacitor (14) is connected to the anode of the one-way trigger diode (15) and the anode of the one-way thyristor (16); the other end of the capacitor (14) is connected to the local ground; the cathode of the one-way trigger diode (15) is connected to an input end of the driving strength calibrator (8), namely, node N21; the cathode of the one-way thyristor (16) is connected to the anode of the diode (19) and to the local ground; the control electrode of the one-way thyristor (16) is connected to one end of the resistor (17); the other end of the resistor (17) is connected to one end of the capacitor (18) and the cathode of the diode (19); the other end of the capacitor (18) is connected to the Fe terminal of the inverter state detector (2).

5. The drive strength calibrator (8) module of the variable current state detector (2) component of the LED light intensity continuously variable stabilizer as described in claim 1 or 2, comprising a diode (20), an N-channel junction field effect transistor (21) and a resistor (22); the drive strength calibrator (8) is characterized in that: it outputs a variable constant current drive pulse, and the drive strength calibrator (8) replaces the old feedback circuit, which can suppress the influence of input power supply fluctuations on the output voltage; wherein, The diode (20) limits the driving strength calibrator (8) to work only during the period when the potential of the Fe terminal is greater than zero; the field effect tube (21) prevents the input power fluctuation from affecting the output current of the driving strength calibrator (8); the resistor (22) adjusts the magnitude of the output current of the driving strength calibrator (8) and constrains the maximum current conversion power of the system; and the Fe terminal of the current conversion state detector (2) is connected to the anode of the diode (20); the cathode of the diode (20), i.e., the node N21, is connected to the drain of the field effect tube (21) and the output end of the oscillation starter (7) module; the source of the field effect tube (21) is connected to one end of the resistor (22); and the other end of the resistor (22) is connected to the gate of the field effect tube (21) and the Dr terminal of the current conversion state detector (2).

6. The switching process accelerator (12) module of the current state detector (2) component of the LED light intensity continuously variable stabilizer as described in claim 1 or 2 comprises a capacitor (31) and a resistor (32); the switching process accelerator (12) is characterized in that: a surge current passes only at the moment of switching of the transistor (36), thereby accelerating the rapid conduction or cutoff of the transistor (36) and reducing the switching loss of the transistor (36); and, the Fe terminal of the current state detector (2) is connected to one end of the capacitor (31); the other end of the capacitor (31) is connected to one end of the resistor (32); and the other end of the resistor (32) is connected to the Dr terminal of the current state detector (2).

7. The charge storage eliminator (10) module of the variable current state detector (2) component of the LED light intensity continuously variable stabilizer as described in claim 1 or 2 comprises diodes (24), (26), a constant current diode (25), and a PNP type transistor (27); the charge storage eliminator (10) is characterized in that it intelligently releases the redundant charge in the transistor (36), further accelerates the rapid cutoff of the transistor (36), and reduces the switching loss of the transistor (36); wherein, The diode (26) limits the stored charge destroyer (10) to operate only during the period when the potential of the Fe terminal is less than zero. The diode (24) provides a reference potential for judging whether the potential of the Dr terminal is slightly less than zero. The constant current diode (25) limits the maximum current of the emitter of the transistor (27) or the conduction voltage of the diode (24). The transistor (27) generates a corresponding emitter current according to the voltage difference between the reference potential and the Dr terminal potential. In addition, the Fe terminal of the variable current state detector (2) is connected to the cathode of the diode (26); the anode of the diode (26) is connected to the cathode of the constant current diode (25) and the collector of the transistor (27); the anode of the constant current diode (25) is connected to the base of the transistor (27) and the cathode of the diode (24); the anode of the diode (24) is connected to the local ground; and the emitter of the transistor (27) is connected to the Dr terminal of the variable current state detector (2).

8. The driving potential regulator (9) module of the variable current state detector (2) component of the LED light intensity continuously variable stabilizer as described in claim 1 or 2 includes a PNP type transistor (23); the driving potential regulator (9) is characterized by: emitter follower type high-speed clamping to stabilize the switching threshold of the transistor (36); and the ReV terminal of the variable current state detector (2) is connected to the base of the transistor (23); the emitter of the transistor (23) is connected to the Dr terminal of the variable current state detector (2); and the collector of the transistor (23) is connected to the local ground.

9. The driving current regulator (11) module of the current state detector (2) component of the LED light intensity continuously variable stabilizer as described in claim 1 or 2, comprising a PNP transistor (28), an NPN transistor (30) and a Schottky diode (29); the driving current regulator (11) is characterized in that: a common base fast shunt is formed by an anti-saturation opposite polarity Darlington transistor, which can adapt to a shorter current conversion cycle; wherein, The transistor (28) can prevent the response speed of the driving current regulation from being slowed down and prevent the output power range of the system from being reduced. The transistor (30) converts the current regulation signal in the potential form into the current form. The Schottky diode (29) prevents the transistor (30) from entering a deep saturation state. In addition, the Dr terminal of the variable current state detector (2) is connected to the emitter of the transistor (28); the base of the transistor (28) is connected to the cathode of the diode (29) and the collector of the transistor (30); the collector of the transistor (28) is connected to the anode of the diode (29) and the base of the transistor (30) and is connected to the local ground; the emitter of the transistor (30) is connected to the ReI terminal of the variable current state detector (2).

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