Crystal oscillator frequency offset determination method, device, equipment, medium and product

Abstract

The invention provides a crystal oscillator frequency offset determination method and device, equipment, a medium and a product, and the method comprises the steps: carrying out the frequency mixing processing of a low local oscillator carrier, and generating a corresponding first frequency mixing result; the low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; the theoretical signal is a downlink signal received when Doppler frequency offset does not occur; performing frequency mixing processing on the high local oscillator carrier to generate a corresponding second frequency mixing result; the high local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; and determining the frequency offset of the crystal oscillator according to the first frequency mixing result and the second frequency mixing result. According to the crystal oscillator frequency offset determination method, the first frequency mixing result is generated after the low local oscillator carrier wave is subjected to frequency mixing processing, the second frequency mixing result is generated after the high local oscillator carrier wave is subjected to frequency mixing processing, and the crystal oscillator frequency offset is determined by utilizing the characteristics of the low local oscillator carrier wave and the high local oscillator carrier wave. Therefore, a mode for determining the frequency offset of the crystal oscillator is provided, and the method does not need to depend on other data such as satellite ephemeris.

Description

Technical Field

[0001] The present application relates to the field of wireless communication technology, and in particular to a method, device, equipment, medium and product for determining a crystal oscillator frequency deviation. Background Art

[0002] In high-speed relative motion, especially in cellular network high-speed rail scenarios and low-orbit satellite communication scenarios, the large Doppler frequency deviation introduced by the high-speed motion and the crystal oscillator frequency deviation introduced by the crystal oscillator accuracy of the communication equipment need to be considered when performing frequency synchronization between communication devices.

[0003] As the crystal oscillator ages, its accuracy decreases, or the frequency accuracy of the crystal oscillator itself is limited. At the same time, since it is difficult for the terminal to determine the frequency deviation of the crystal oscillator, when the uplink signal sent by the terminal reaches the base station, there is still a large range of frequency deviation, causing the uplink random access performance to deteriorate or even fail to access.

[0004] Therefore, there is currently a problem that the uplink signal has a large frequency deviation due to the difficulty in determining the crystal oscillator frequency deviation. Summary of the invention

[0005] The present application provides a crystal oscillator frequency deviation determination method, device, equipment, medium and product, which are used to solve the problem that the uplink signal has a large range of frequency deviation due to the difficulty in determining the crystal oscillator frequency deviation.

[0006] A first aspect of the present application provides a method for determining a crystal oscillator frequency deviation, comprising:

[0007] Performing mixing processing on the low local oscillator carrier to generate a corresponding first mixing result; the low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; the theoretical signal is a downlink signal received when no Doppler frequency shift occurs;

[0008] Performing mixing processing on the high local oscillator carrier to generate a corresponding second mixing result; the high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal;

[0009] The crystal oscillator frequency deviation is determined according to the first mixing result and the second mixing result.

[0010] Furthermore, in the above method, the mixing process is performed on the low local oscillator carrier to generate a corresponding first mixing result, including:

[0011] The low local oscillator carrier and the first actual signal are mixed and processed to generate a complex signal to generate a first in-phase orthogonal IQ complex signal; the first actual signal is a first downlink signal received when a Doppler frequency shift occurs;

[0012] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding first mixing result.

[0013] Furthermore, in the above method, the mixing of the low local oscillator carrier and the first actual signal and the complex signal generation process to generate the first in-phase orthogonal IQ complex signal includes:

[0014] Performing analog mixing processing on the low local oscillator carrier and the first actual signal to generate a first intermediate signal;

[0015] Using a low-pass filter to perform low-pass filtering on the first intermediate signal to generate a second intermediate signal;

[0016] The second intermediate signal is sampled by an analog-to-digital converter to generate a first IQ complex signal.

[0017] Furthermore, in the method as described above, the first IQ complex signal and the preset intermediate frequency signal are subjected to digital mixing processing and digital down-conversion processing to generate a corresponding first mixing result, including:

[0018] Performing digital mixing processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding third intermediate signal;

[0019] The third intermediate signal is subjected to negative frequency filtering and down-sampling processing to generate a corresponding first mixing result.

[0020] Furthermore, in the above method, the mixing process is performed on the high local oscillator carrier to generate a corresponding second mixing result, including:

[0021] The high local oscillator carrier and the second actual signal are mixed and processed to generate a complex signal to generate a second IQ complex signal; the second actual signal is a second downlink signal received when a Doppler frequency shift occurs;

[0022] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding second mixing result.

[0023] Furthermore, in the above method, the mixing of the high local oscillator carrier and the second actual signal and the complex signal generation process to generate the second IQ complex signal includes:

[0024] Performing analog mixing processing on the high local oscillator carrier and the second actual signal to generate a fourth intermediate signal;

[0025] low-pass filtering the fourth intermediate signal using a low-pass filter to generate a fifth intermediate signal;

[0026] The fifth intermediate signal is sampled by an analog-to-digital converter to generate a second IQ complex signal.

[0027] Furthermore, in the above method, the step of performing digital mixing and digital down-conversion on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result includes:

[0028] Performing digital mixing processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding sixth intermediate signal;

[0029] The sixth intermediate signal is subjected to negative frequency filtering and down-sampling processing to generate a corresponding second mixing result.

[0030] Further, in the method as described above, the first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal when they are received.

[0031] Furthermore, in the method as described above, determining the crystal oscillator frequency deviation according to the first mixing result and the second mixing result includes:

[0032] The first mixing result, the second mixing result and the preset intermediate frequency are input into a preset crystal oscillator frequency deviation calculation algorithm, and the crystal oscillator frequency deviation is determined using the preset crystal oscillator frequency deviation calculation algorithm; the preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0033] Furthermore, the method as described above further comprises:

[0034] Inputting the first mixing result, the second mixing result, the theoretical signal frequency and the preset intermediate frequency into a preset Doppler frequency deviation algorithm, and using the preset Doppler frequency deviation algorithm to determine the Doppler frequency deviation; the theoretical signal frequency is the frequency of the theoretical signal;

[0035] The first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency are input into a preset crystal oscillator uncertainty algorithm, and the preset crystal oscillator uncertainty algorithm is used to determine the crystal oscillator uncertainty; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0036] Furthermore, the method as described above, after inputting the first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency into a preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty, further includes:

[0037] Inputting the crystal oscillator uncertainty, Doppler frequency deviation, and theoretical signal frequency into a preset compensation algorithm, and using the preset compensation algorithm to generate an uplink compensation frequency;

[0038] The uplink generated signal is frequency compensated according to the uplink compensation frequency.

[0039] A second aspect of the present application provides a crystal oscillator frequency deviation determination device, comprising:

[0040] A first frequency mixing module, used for performing frequency mixing processing on a low local oscillator carrier to generate a corresponding first frequency mixing result; the low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; the theoretical signal is a downlink signal received when no Doppler frequency shift occurs;

[0041] A second frequency mixing module, used for performing frequency mixing processing on a high local oscillator carrier to generate a corresponding second frequency mixing result; the high local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal;

[0042] A determination module is used to determine a crystal oscillator frequency deviation according to the first mixing result and the second mixing result.

[0043] Further, in the above device, the first frequency mixing module is specifically used for:

[0044] The low local oscillator carrier and the first actual signal are mixed and processed for complex signal generation to generate a first in-phase orthogonal IQ complex signal; the first actual signal is a first downlink signal received when a Doppler frequency shift occurs; the first IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding first mixing result.

[0045] Further, in the above-mentioned device, when the first mixing module performs mixing and complex signal generation processing on the low local oscillator carrier and the first actual signal to generate the first in-phase orthogonal IQ complex signal, it is specifically used to:

[0046] The low local oscillator carrier and the first actual signal are subjected to analog mixing processing to generate a first intermediate signal; the first intermediate signal is subjected to low-pass filtering processing using a low-pass filter to generate a second intermediate signal; the second intermediate signal is sampled using an analog-to-digital converter to generate a first IQ complex signal.

[0047] Further, in the above-mentioned device, when the first mixing module performs digital mixing processing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding first mixing result, it is specifically used to:

[0048] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate a corresponding third intermediate signal; the third intermediate signal is negatively frequency filtered and down-sampled to generate a corresponding first mixing result.

[0049] Further, in the above device, the second frequency mixing module is specifically used for:

[0050] The high local oscillator carrier and the second actual signal are mixed and processed for complex signal generation to generate a second IQ complex signal; the second actual signal is a second downlink signal received when a Doppler frequency shift occurs; the second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding second mixing result.

[0051] Further, in the above-mentioned device, when the second mixing module performs mixing and complex signal generation processing on the high local oscillator carrier and the second actual signal to generate the second IQ complex signal, it is specifically used to:

[0052] The high local oscillator carrier and the second actual signal are subjected to analog mixing processing to generate a fourth intermediate signal; the fourth intermediate signal is subjected to low-pass filtering processing using a low-pass filter to generate a fifth intermediate signal; and the fifth intermediate signal is sampled using an analog-to-digital converter to generate a second IQ complex signal.

[0053] Further, in the above-described device, when the second mixing module performs digital mixing processing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result, it is specifically used to:

[0054] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate a corresponding sixth intermediate signal; the sixth intermediate signal is negatively frequency filtered and down-sampled to generate a corresponding second mixing result.

[0055] Further, in the above-mentioned device, the first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal when they are received.

[0056] Further, in the above device, the determining module is specifically used for:

[0057] The first mixing result, the second mixing result and the preset intermediate frequency are input into a preset crystal oscillator frequency deviation calculation algorithm, and the crystal oscillator frequency deviation is determined using the preset crystal oscillator frequency deviation calculation algorithm; the preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0058] Furthermore, the device as described above further comprises:

[0059] A frequency deviation determination module, used for inputting the first mixing result, the second mixing result, the theoretical signal frequency and the preset intermediate frequency into a preset Doppler frequency deviation algorithm, and using the preset Doppler frequency deviation algorithm to determine the Doppler frequency deviation; the theoretical signal frequency is the frequency of the theoretical signal;

[0060] The uncertainty determination module is used to input the first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency into a preset crystal oscillator uncertainty algorithm, and use the preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0061] Furthermore, the device as described above further comprises:

[0062] The compensation module is used to input the crystal oscillator uncertainty, Doppler frequency deviation, and theoretical signal frequency into a preset compensation algorithm, and use the preset compensation algorithm to generate an uplink compensation frequency; and perform frequency compensation on the uplink generated signal according to the uplink compensation frequency.

[0063] A third aspect of the present application provides a communication device, including: a memory and a processor;

[0064] The memory stores computer-executable instructions;

[0065] The processor executes the computer-executable instructions stored in the memory to implement the crystal oscillator frequency deviation determination method as described in any one of the first aspects.

[0066] A fourth aspect of the present application provides a computer-readable storage medium, wherein the computer-readable storage medium stores computer-executable instructions, and when the computer-executable instructions are executed by a processor, they are used to implement the crystal oscillator frequency deviation determination method described in any one of the first aspects.

[0067] A fifth aspect of the present application provides a computer program product, including a computer program, which, when executed by a processor, implements the crystal oscillator frequency deviation determination method described in any one of the first aspects.

[0068] The present application provides a method, device, equipment, medium and product for determining the frequency deviation of a crystal oscillator, the method comprising: performing mixing processing on a low local oscillator carrier to generate a corresponding first mixing result; the low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; the theoretical signal is a downlink signal received when no Doppler frequency deviation occurs; performing mixing processing on a high local oscillator carrier to generate a corresponding second mixing result; the high local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal; and determining the crystal oscillator frequency deviation according to the first mixing result and the second mixing result. The method for determining the frequency deviation of a crystal oscillator of the present application determines the frequency deviation of the crystal oscillator by mixing the low local oscillator carrier to generate a first mixing result and mixing the high local oscillator carrier to generate a second mixing result, and by using the characteristics of the low local oscillator carrier and the high local oscillator carrier. Thus, a method for determining the frequency deviation of the crystal oscillator is provided without relying on other data such as satellite data, thereby reducing the frequency deviation of the uplink signal. BRIEF DESCRIPTION OF THE DRAWINGS

[0069] The accompanying drawings, which are incorporated in and constitute a part of this specification, illustrate embodiments consistent with the present application and, together with the description, serve to explain the principles of the present application.

[0070] Figure 1 A schematic diagram of the device structure of the crystal oscillator frequency deviation determination method provided in this application;

[0071] Figure 2 Schematic diagram of the process of determining the crystal oscillator frequency deviation provided in this application Figure 1 ;

[0072] Figure 3 Schematic diagram of the process of determining the crystal oscillator frequency deviation provided in this application Figure 2 ;

[0073] Figure 4a A mixing diagram of the crystal oscillator frequency deviation determination method provided in this application Figure 1 ;

[0074] Figure 4b A mixing diagram of the crystal oscillator frequency deviation determination method provided in this application Figure 2 ;

[0075] Figure 4c A mixing diagram of the crystal oscillator frequency deviation determination method provided in this application Figure 3 ;

[0076] Figure 5 A schematic diagram of the structure of the crystal oscillator frequency deviation determination device provided in this application;

[0077] Figure 6 A schematic diagram of the structure of the communication device provided in this application.

[0078] The above drawings have shown clear embodiments of the present application, which will be described in more detail later. These drawings and text descriptions are not intended to limit the scope of the present application in any way, but to illustrate the concept of the present application to those skilled in the art by referring to specific embodiments. DETAILED DESCRIPTION

[0079] Exemplary embodiments will be described in detail herein, examples of which are shown in the accompanying drawings. When the following description refers to the drawings, the same numbers in different drawings represent the same or similar elements unless otherwise indicated. The implementations described in the following exemplary embodiments do not represent all implementations consistent with the present application. Instead, they are merely examples of devices and methods consistent with some aspects of the present application as detailed in the appended claims.

[0080] The technical solution of the present application is described in detail with specific embodiments below. The following specific embodiments can be combined with each other, and the same or similar concepts or processes may not be repeated in some embodiments. The embodiments of the present application will be described below in conjunction with the accompanying drawings.

[0081] In order to clearly understand the technical solution of the present application, the conception process of the technical solution is first introduced in detail. The high-speed relative movement of the communication transceiver will introduce a large range of Doppler frequency deviation, which brings huge challenges to frequency synchronization, especially in the cellular network high-speed rail scenario and low-orbit satellite communication scenario. The terminal located on the high-speed rail and the base station on the satellite will introduce a large Doppler frequency deviation due to high-speed movement. In the initial access stage, after the terminal completes the initial downlink time-frequency synchronization based on the downlink broadcast signal, it is necessary to estimate the pre-compensation value of the uplink transmission frequency based on downlink measurement or other auxiliary means, so that when the uplink random access signal reaches the base station after compensation, the signal frequency is within the frequency range allowed by the base station, thereby ensuring the success rate of uplink random access and reducing the waiting time for users to enter the network.

[0082] Since the terminal cannot distinguish the frequency components from the downlink frequency deviation estimation result, it is difficult to determine the crystal oscillator frequency deviation, which will cause the pre-compensated uplink signal to still have a large range of frequency deviation when it reaches the base station, causing the uplink random access performance to deteriorate or even fail to access.

[0083] Therefore, there is currently a problem that the uplink signal has a large frequency deviation due to the difficulty in determining the crystal oscillator frequency deviation.

[0084] Therefore, in view of the problem that it is difficult to determine the crystal oscillator frequency deviation in the prior art, resulting in a large range of frequency deviation in the uplink signal, the inventors found in their research that the crystal oscillator frequency deviation can be determined by the low local oscillator carrier and the high local oscillator carrier characteristics. By mixing the target signal to the required low intermediate frequency and then extracting the signal through low-pass filtering, two reception results for the same signal or two consecutive signals with similar time are obtained, namely the first mixing result and the second mixing result, so that the crystal oscillator frequency deviation is determined based on the first mixing result and the second mixing result.

[0085] Specifically, the process of determining the crystal oscillator frequency deviation is as follows:

[0086] The low local oscillator carrier is mixed to generate a corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal. The theoretical signal is a downlink signal received when no Doppler frequency deviation occurs. The high local oscillator carrier is mixed to generate a corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal. The crystal oscillator frequency deviation is determined according to the first mixing result and the second mixing result.

[0087] The crystal oscillator frequency deviation determination method of the present application generates a first mixing result after mixing the low local oscillator carrier and generates a second mixing result after mixing the high local oscillator carrier, and determines the crystal oscillator frequency deviation using the characteristics of the low local oscillator carrier and the high local oscillator carrier. Thus, a method for determining the crystal oscillator frequency deviation is provided without relying on other data such as satellite navigation, satellite ephemeris, etc., and without multiple interactions with the base station.

[0088] Based on the above creative findings, the inventor proposed the technical solution of the present application.

[0089] The following describes the application scenarios of the method for determining the crystal oscillator frequency deviation provided in the embodiment of the present application. Figure 1 As shown in the figure, a partial structure of a communication device 10 is exemplarily shown. In the figure, the communication device 10 includes an antenna 11, a radio frequency chip 12, and a baseband 13. The radio frequency chip 12 includes multiple components not shown in the figure, such as a bandpass filter, a low-pass filter, a low-noise amplifier, an analog-to-digital converter, etc. The baseband 13 includes multiple components not shown in the figure, such as a frequency synchronization module, digital down-conversion related components, etc.

[0090] Exemplarily, when receiving a downlink signal, the communication device 10 receives the signal through the antenna 11. At this time, the downlink signal is processed by the radio frequency chip 12 and then transmitted to the baseband 13. In order to accurately pre-compensate the uplink signal, the communication device 10 performs the following crystal oscillator frequency deviation determination process:

[0091] ① After the downlink signal is pre-processed by bandpass filtering, low noise amplifier processing, etc., the downlink signal is divided by the local crystal oscillator to generate a low local oscillator carrier and a high local oscillator carrier. At this time, the frequency division is based on the theoretical signal and the preset intermediate frequency signal. The theoretical signal is the downlink signal received when no Doppler frequency shift occurs, and the preset intermediate frequency signal is the intermediate frequency frequency allowed to be configured when performing orthogonal demodulation under the low intermediate frequency structure.

[0092] ② Perform mixing processing on the low local oscillator carrier to generate the corresponding first mixing result.

[0093] ③ Perform mixing processing on the high local oscillator carrier to generate a corresponding second mixing result.

[0094] ④ Determine the crystal oscillator frequency deviation based on the first mixing result and the second mixing result.

[0095] After the crystal oscillator frequency deviation is determined, the crystal oscillator uncertainty and the Doppler frequency deviation may be further determined in a manner similar to step ④ of this embodiment.

[0096] The embodiments of the present application are introduced below in conjunction with the drawings in the specification.

[0097] Figure 2 Schematic diagram of the process of determining the crystal oscillator frequency deviation provided in this application Figure 1,like Figure 2 As shown, the execution subject of the embodiment of the present application is a crystal oscillator frequency deviation determination device, which can be integrated in a communication device, such as a terminal device. The crystal oscillator frequency deviation determination method provided in this embodiment includes the following steps:

[0098] Step S101, mixing the low local oscillator carrier to generate a corresponding first mixing result. The low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal. The theoretical signal is a downlink signal received when no Doppler frequency shift occurs.

[0099] In this embodiment, when a communication device such as a terminal receives a downlink signal, it receives the downlink signal transmission at a known frequency. If the influence of Doppler frequency deviation is not considered for the downlink signal corresponding to the known frequency, it can be considered that no Doppler frequency deviation occurs. At this time, the corresponding downlink signal is the aforementioned theoretical signal. In the actual process, the downlink signal will introduce Doppler frequency deviation during the transmission process, and the frequency of the actual signal is the sum of the known frequency and the Doppler frequency deviation.

[0100] For example, it is assumed that the downlink signal sent by the base station to the terminal is at a frequency f c During the wireless transmission process, the Doppler frequency shift f caused by the relative motion between the base station and the terminal will be introduced. d , so the carrier frequency of the downlink signal reaching the terminal antenna becomes f ue =f c +f d The theoretical signal is of frequency f c .

[0101] In this embodiment, the preset intermediate frequency signal can be an intermediate frequency that can be configured when performing orthogonal demodulation under a low intermediate frequency structure. The low local oscillator carrier can be obtained by dividing the theoretical signal and the preset intermediate frequency signal through a local crystal oscillator. For example, if the theoretical signal is a frequency f c , the preset intermediate frequency signal is f IF , the theoretical low local oscillator carrier is The low LO carrier is Then the theoretical low local oscillator carrier is In the generated frequency Due to the uncertainty of the crystal oscillator x ppm (unit of crystal oscillator accuracy, one millionth), the low local oscillator carrier in, The crystal offset frequency of the low local oscillator.

[0102] Optionally, in this embodiment, the mixing process of the low local oscillator carrier may include processing procedures such as mixing, filtering, and noise reduction. The mixing may be multiple mixings, such as performing initial mixing based on the frequency of the actual signal, and subsequently performing digital mixing to obtain the final first mixing result.

[0103] Step S102, mixing the high local oscillator carrier to generate a corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal.

[0104] In this embodiment, the high local oscillator carrier is similar to the low local oscillator carrier, and the high local oscillator carrier can be obtained by dividing the local crystal oscillator based on the theoretical signal and the preset intermediate frequency signal.

[0105] For example, if the theoretical signal is of frequency f c , the preset intermediate frequency signal is f IF , the theoretical high local oscillator carrier is The high LO carrier is Then the theoretical high local oscillator carrier is In the generated frequency Due to the uncertainty of the crystal oscillator xppm (unit of crystal oscillator accuracy, one millionth), the high local oscillator carrier in, is the crystal oscillator bias frequency of the high local oscillator, let but It can be expressed as:

[0106]

[0107] Optionally, in this embodiment, the mixing process of the high local oscillator carrier may include processing procedures such as mixing, filtering, and noise reduction. The mixing may be multiple mixings, such as performing initial mixing based on the frequency of the actual signal, and subsequently performing digital mixing to obtain a final second mixing result.

[0108] Step S103, determining the crystal oscillator frequency deviation according to the first mixing result and the second mixing result.

[0109] In this embodiment, since the first mixing result is related to the low local oscillator carrier and the second mixing result is related to the high local oscillator carrier, and it can be known from the theoretical signal and the preset intermediate frequency signal that the crystal oscillator frequency deviation can be determined based on the first mixing result and the second mixing result through the preset crystal oscillator frequency deviation calculation algorithm.

[0110] A method for determining a crystal oscillator frequency deviation is provided in an embodiment of the present application, and the method includes: performing mixing processing on a low local oscillator carrier to generate a corresponding first mixing result. The low local oscillator carrier is generated based on a received theoretical signal and a preset intermediate frequency signal. The theoretical signal is a downlink signal received when no Doppler frequency deviation occurs. Performing mixing processing on a high local oscillator carrier to generate a corresponding second mixing result. The high local oscillator carrier is generated based on the received theoretical signal and a preset intermediate frequency signal. The crystal oscillator frequency deviation is determined based on the first mixing result and the second mixing result.

[0111] The crystal oscillator frequency deviation determination method of the present application generates a first mixing result after mixing a low local oscillator carrier and generates a second mixing result after mixing a high local oscillator carrier, and determines the crystal oscillator frequency deviation using the characteristics of the low local oscillator carrier and the high local oscillator carrier. Thus, a method for determining the crystal oscillator frequency deviation is provided without relying on other data such as satellite data.

[0112] Figure 3 Schematic diagram of the process of determining the crystal oscillator frequency deviation provided in this application Figure 2 ,like Figure 3 As shown, the crystal oscillator frequency deviation determination method provided in this embodiment is further refined on the basis of the crystal oscillator frequency deviation determination method provided in the previous embodiment of the present application, and the crystal oscillator frequency deviation determination method provided in this embodiment includes the following steps.

[0113] Step S201, mixing the low local oscillator carrier and the first actual signal and performing complex signal generation processing to generate a first in-phase orthogonal IQ complex signal. The first actual signal is a first downlink signal received when Doppler frequency shift occurs.

[0114] In this embodiment, the frequency of the first actual signal is the sum of the frequency of the theoretical signal and the Doppler frequency shift, that is, f in the previous embodiment. ue By mixing the low local oscillator carrier and the first actual signal and performing complex signal generation processing, the in-phase and quadrature IQ complex signals required for subsequent use can be obtained, providing a basis for subsequent determination of the crystal oscillator frequency deviation, where I represents in-phase and Q represents quadrature.

[0115] Optionally, in this embodiment, S201 may include the following process:

[0116] The low local oscillator carrier and the first actual signal are subjected to analog mixing processing to generate a first intermediate signal.

[0117] The first intermediate signal is subjected to low-pass filtering by using a low-pass filter to generate a second intermediate signal.

[0118] The second intermediate signal is sampled by an analog-to-digital converter to generate a first IQ complex signal.

[0119] In this embodiment, analog mixing processing refers to mixing processing performed in the analog domain, and the analog mixing processing can be implemented by a radio frequency chip. After analog mixing, high-frequency components and low-frequency components can be obtained, that is, there are high-frequency components and low-frequency components in the first intermediate signal. At this time, the first intermediate signal is low-pass filtered by a low-pass filter to retain the low-frequency component, that is, the second intermediate signal is a signal corresponding to the low-frequency component. At the same time, the second intermediate signal is sampled by an analog-to-digital converter to generate a first IQ complex signal, which can be further processed by the baseband.

[0120] Exemplarily, in this embodiment, the frequency of the theoretical signal is as follows Figure 4a As shown, the filled box with diagonal lines represents negative frequency. When analog mixing is performed, the first intermediate signal is generated as shown in Figure 4b As shown in the figure, LPF is a low-pass filter, the full name is Low Pass Filter, and the dotted box part represents the low-pass filter team filtering the first intermediate signal to retain the low-frequency component.

[0121] Step S202: Perform digital mixing and digital down-conversion on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding first mixing result.

[0122] In this embodiment, digital mixing processing refers to digital mixing performed in the digital domain. The baseband can perform digital mixing processing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to obtain a signal that meets the baseband synchronization requirement and a first mixing result.

[0123] Optionally, in this embodiment, S202 may include the following process:

[0124] The first IQ complex signal and a preset intermediate frequency signal are digitally mixed to generate a corresponding third intermediate signal.

[0125] The third intermediate signal is subjected to negative frequency filtering and down-sampling processing to generate a corresponding first mixing result.

[0126] In this embodiment, the preset intermediate frequency signal used in the digital mixing process may be a negative frequency. For example, the negative frequency f mix =-f IF Through this digital mixing, the digital signal required for the baseband, namely the third intermediate signal, can be obtained.

[0127] At the same time, after negative frequency filtering and downsampling, a digital baseband signal with the required rate of the baseband frequency synchronization module can be obtained. At this time, the first mixing result can also be called the total frequency deviation Δf1 of the first mixing:

[0128]

[0129] Among them, f ue is the carrier frequency of the first actual signal, is the frequency of the low local oscillator carrier, f mix is the negative frequency mentioned above, f c is the frequency of the theoretical signal, f d is the Doppler frequency shift, f IF It is the preset intermediate frequency signal.

[0130] Step S203: Mix the high local oscillator carrier and the second actual signal and perform complex signal generation processing to generate a second IQ complex signal. The second actual signal is a second downlink signal received when Doppler frequency shift occurs.

[0131] In this embodiment, the frequency of the second actual signal is the sum of the frequency of the theoretical signal and the Doppler frequency shift. The frequency of the second actual signal can also be expressed as f in the previous embodiment. ue The second actual signal can be the same as or different from the first actual signal. By mixing the high local oscillator carrier and the second actual signal and generating a complex signal, the in-phase orthogonal IQ complex signal required for subsequent use can be obtained, providing a basis for the subsequent determination of the crystal oscillator frequency deviation.

[0132] Optionally, the first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal when they are received. The preset time difference can be set according to the accuracy requirements of the crystal oscillator frequency deviation in actual application. If the highest accuracy is required, the preset time difference can be set to zero, that is, the first actual signal is the same as the second actual signal. When the first actual signal is the same as the second actual signal, the Doppler frequency deviation of the two is the same, and when there is a preset time difference between the first actual signal and the second actual signal when they are received, the Doppler frequency deviation of the two is different, but the difference between the two is small.

[0133] Optionally, in this embodiment, S203 may include the following process:

[0134] The high local oscillator carrier and the second actual signal are subjected to analog mixing processing to generate a fourth intermediate signal.

[0135] The fourth intermediate signal is subjected to low-pass filtering by using a low-pass filter to generate a fifth intermediate signal.

[0136] The fifth intermediate signal is sampled by an analog-to-digital converter to generate a second IQ complex signal.

[0137] In this embodiment, similar to the process of low local oscillator carrier mixing, analog mixing processing can be implemented by a radio frequency chip. After analog mixing, high-frequency components and low-frequency components can be obtained, that is, there are high-frequency components and low-frequency components in the fourth intermediate signal. At this time, the fourth intermediate signal is low-pass filtered by a low-pass filter to retain the low-frequency component, that is, the fifth intermediate signal is a signal corresponding to the low-frequency component. At the same time, the fifth intermediate signal is sampled by an analog-to-digital converter to generate a second IQ complex signal, which can be further processed by the baseband.

[0138] Exemplarily, in this embodiment, the frequency of the theoretical signal is as follows Figure 4a As shown, the diagonal filled box represents the negative frequency. When analog mixing is performed, the fourth intermediate signal is generated as shown in Figure 4cAs shown, LPF is a low-pass filter, and the dotted box part represents that the low-pass filter filters the fourth intermediate signal to retain the low-frequency component.

[0139] Step S204: digitally mix and digitally down-convert the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result.

[0140] In this embodiment, the baseband may perform digital mixing processing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to obtain a signal that meets the baseband synchronization requirement and a second mixing result.

[0141] Optionally, in this embodiment, S204 may include the following process:

[0142] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate a corresponding sixth intermediate signal.

[0143] The sixth intermediate signal is subjected to negative frequency filtering and down-sampling processing to generate a corresponding second mixing result.

[0144] In this embodiment, the preset intermediate frequency signal used in the digital mixing process may be a negative frequency. For example, the negative frequency f mix =-f IF Through this digital mixing, the digital signal required for the baseband, namely the sixth intermediate signal, can be obtained.

[0145] At the same time, after negative frequency filtering and downsampling, a digital baseband signal with the rate required by the frequency synchronization module in the baseband can be obtained. At this time, the second mixing result can also be called the total frequency deviation Δf2 of the second mixing:

[0146]

[0147] Among them, f ue is the frequency of the second actual signal, is the frequency of the high local oscillator carrier, f mix is the negative frequency mentioned above, f c is the frequency of the theoretical signal, f d is the Doppler frequency shift, f IF is the preset intermediate frequency signal, ε is ratio.

[0148] Step S205, inputting the first mixing result, the second mixing result and the preset intermediate frequency into a preset crystal oscillator frequency deviation calculation algorithm, and using the preset crystal oscillator frequency deviation calculation algorithm to determine the crystal oscillator frequency deviation. The preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0149] In this embodiment, the preset crystal oscillator frequency deviation calculation algorithm can be as follows:

[0150]

[0151] in, is the crystal oscillator offset frequency of the low local oscillator, is the theoretical low local oscillator carrier, x is the uncertainty of the crystal oscillator, is the crystal oscillator offset frequency of the high local oscillator, is the theoretical high local oscillator carrier.

[0152] Optionally, in this embodiment, the Doppler frequency deviation and the crystal oscillator uncertainty may also be determined, as follows:

[0153] The first mixing result, the second mixing result, the theoretical signal frequency and the preset intermediate frequency are input into the preset Doppler frequency deviation algorithm, and the preset Doppler frequency deviation algorithm is used to determine the Doppler frequency deviation. The theoretical signal frequency is the frequency of the theoretical signal.

[0154] The first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency are input into the preset crystal oscillator uncertainty algorithm, and the crystal oscillator uncertainty is determined using the preset crystal oscillator uncertainty algorithm. The low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0155] In this embodiment, the preset Doppler frequency shift algorithm may be as follows:

[0156]

[0157] The preset crystal uncertainty algorithm can be as follows:

[0158]

[0159] or

[0160]

[0161] Optionally, in this embodiment, after the crystal oscillator uncertainty is determined, the uplink signal may be further compensated as follows:

[0162] The crystal oscillator uncertainty, Doppler frequency deviation, and theoretical signal frequency are input into a preset compensation algorithm, and the preset compensation algorithm is used to generate an uplink compensation frequency.

[0163] The frequency of the uplink generated signal is compensated according to the uplink compensation frequency.

[0164] In this embodiment, the preset compensation algorithm may be as follows:

[0165]

[0166] in, is the compensation frequency, f tis the uplink signal frequency, is the upstream crystal oscillator frequency deviation, is the uplink Doppler frequency deviation.

[0167] After the frequency compensation of the uplink signal is performed by the uplink compensation frequency, the frequency of the uplink signal reaching the transmission target can be close to the expected transmission frequency f t .

[0168] Optionally, if the baseband mixing module of the communication device can support the sampling rate High enough to satisfy the Nyquist sampling theorem, that is, to satisfy:

[0169]

[0170] Among them, w s If the uplink signal bandwidth is the uplink frequency pre-compensation, the uplink frequency pre-compensation can be realized at the digital mixing point of the baseband, and the pre-compensated baseband signal is then transmitted at the carrier frequency f t Based on this compensation method, when the downlink frequency offset is estimated accurately, both the uplink crystal oscillator frequency offset and the uplink Doppler frequency offset can be accurately compensated.

[0171] Optionally, if the baseband sampling rate cannot meet the requirements of digital mixing, the uplink frequency pre-compensation needs to be implemented at the analog mixing point of the intermediate frequency. At this time, the signal is corrected by the pre-compensated carrier frequency f tx send:

[0172]

[0173] Based on this compensation method, since the corrected carrier frequency f tx The corresponding crystal frequency deviation will become f tx ×10 -6 ×x, therefore, after the uplink signal is introduced into the uplink crystal oscillator frequency deviation and the uplink Doppler frequency deviation and arrives at the base station side, it is different from the expected frequency f t There is a small deviation Δf between t :

[0174]

[0175] But generally Δf t It is usually only at the Hz level, so the impact on the uplink open-loop frequency synchronization is negligible.

[0176] The crystal oscillator frequency deviation determination method of this embodiment first receives a carrier frequency of f cThe real signal is then mixed to the desired low intermediate frequency by the RF front end of the low intermediate frequency structure using high and low local oscillators, and then the signal is taken out through low-pass filtering, thereby obtaining two reception results for the same signal. Since the mixing results are obtained by performing two analog mixing on the same signal or two consecutive signals of the same frequency at similar times, the Doppler frequency deviations carried by the two signals themselves remain unchanged or almost unchanged, and the two high and low local oscillator carriers obtained by the terminal through crystal oscillator frequency division carry two observations of the uncertainty of the crystal oscillator, so the crystal oscillator frequency deviation can be calculated based on these two downlink frequency deviation measurements.

[0177] The crystal oscillator frequency deviation determination method of this embodiment enables communication equipment such as a terminal to estimate the terminal's downlink crystal oscillator frequency deviation and uplink frequency pre-compensation value without relying on GNSS (Global Navigation Satellite System), satellite ephemeris, and multiple interactions with base stations, thereby accurately compensating the uplink transmission frequency, improving the performance of uplink open-loop frequency synchronization, and ensuring the success rate of initial uplink random access.

[0178] Figure 5 The structure diagram of the crystal oscillator frequency deviation determination device provided in this application is as follows: Figure 5 As shown, in this embodiment, the crystal oscillator frequency deviation determining device 300 can be set in a communication device, and the crystal oscillator frequency deviation determining device 300 includes:

[0179] The first mixing module 301 is used to perform mixing processing on the low local oscillator carrier to generate a corresponding first mixing result. The low local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal. The theoretical signal is the downlink signal received when no Doppler frequency shift occurs.

[0180] The second frequency mixing module 302 is used to perform frequency mixing processing on the high local oscillator carrier to generate a corresponding second frequency mixing result. The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal.

[0181] The determination module 303 is used to determine the crystal oscillator frequency deviation according to the first mixing result and the second mixing result.

[0182] The crystal oscillator frequency deviation determination device provided in this embodiment can be executed Figure 2 The technical solution of the method embodiment shown in the figure has the same implementation principle and technical effect as Figure 2 The method embodiments shown are similar and will not be described in detail here.

[0183] The crystal oscillator frequency deviation determining device provided in the present application is further refined on the basis of the crystal oscillator frequency deviation determining device provided in the previous embodiment, and the crystal oscillator frequency deviation determining device 300 includes:

[0184] Optionally, in this embodiment, the first frequency mixing module 301 is specifically used for:

[0185] The low local oscillator carrier and the first actual signal are mixed and processed for complex signal generation to generate a first in-phase orthogonal IQ complex signal. The first actual signal is a first downlink signal received when Doppler frequency shift occurs. The first IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding first mixing result.

[0186] Optionally, in this embodiment, when the first mixing module 301 performs mixing and complex signal generation processing on the low local oscillator carrier and the first actual signal to generate the first in-phase orthogonal IQ complex signal, it is specifically used to:

[0187] The low local oscillator carrier and the first actual signal are subjected to analog mixing processing to generate a first intermediate signal. The first intermediate signal is subjected to low-pass filtering processing using a low-pass filter to generate a second intermediate signal. The second intermediate signal is sampled using an analog-to-digital converter to generate a first IQ complex signal.

[0188] Optionally, in this embodiment, when the first mixing module 301 performs digital mixing processing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding first mixing result, it is specifically used to:

[0189] The first IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate a corresponding third intermediate signal. The third intermediate signal is negatively filtered and downsampled to generate a corresponding first mixing result.

[0190] Optionally, in this embodiment, the second frequency mixing module 302 is specifically used for:

[0191] The high local oscillator carrier and the second actual signal are mixed and processed to generate a complex signal to generate a second IQ complex signal. The second actual signal is a second downlink signal received when a Doppler frequency shift occurs. The second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding second mixing result.

[0192] Optionally, in this embodiment, when the second mixing module 302 performs mixing and complex signal generation processing on the high local oscillator carrier and the second actual signal to generate the second IQ complex signal, it is specifically used to:

[0193] The high local oscillator carrier and the second actual signal are subjected to analog mixing processing to generate a fourth intermediate signal. The fourth intermediate signal is subjected to low-pass filtering processing using a low-pass filter to generate a fifth intermediate signal. The fifth intermediate signal is sampled using an analog-to-digital converter to generate a second IQ complex signal.

[0194] Optionally, in this embodiment, when the second mixing module 302 performs digital mixing processing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result, it is specifically used to:

[0195] The second IQ complex signal and the preset intermediate frequency signal are digitally mixed to generate a corresponding sixth intermediate signal. The sixth intermediate signal is negatively frequency filtered and downsampled to generate a corresponding second mixing result.

[0196] Optionally, in this embodiment, the first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal when they are received.

[0197] Optionally, in this embodiment, the determining module 303 is specifically used for:

[0198] The first mixing result, the second mixing result and the preset intermediate frequency are input into the preset crystal oscillator frequency deviation calculation algorithm, and the crystal oscillator frequency deviation is determined by using the preset crystal oscillator frequency deviation calculation algorithm. The preset intermediate frequency is the frequency of the preset intermediate frequency signal.

[0199] Optionally, in this embodiment, the crystal oscillator frequency deviation determining device 300 further includes:

[0200] The frequency deviation determination module is used to input the first mixing result, the second mixing result, the theoretical signal frequency and the preset intermediate frequency into the preset Doppler frequency deviation algorithm, and use the preset Doppler frequency deviation algorithm to determine the Doppler frequency deviation. The theoretical signal frequency is the frequency of the theoretical signal.

[0201] The uncertainty determination module is used to input the first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency into the preset crystal oscillator uncertainty algorithm, and use the preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty. The low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

[0202] Optionally, in this embodiment, the crystal oscillator frequency deviation determining device 300 further includes:

[0203] The compensation module is used to input the crystal oscillator uncertainty, Doppler frequency deviation, and theoretical signal frequency into a preset compensation algorithm, and use the preset compensation algorithm to generate an uplink compensation frequency. The frequency compensation of the uplink generated signal is performed according to the uplink compensation frequency.

[0204] The crystal oscillator frequency deviation determination device provided in this embodiment can be executed Figure 2 -The technical solution of the method embodiment shown in FIG4, its implementation principle and technical effect are similar to Figure 2 -The method embodiment shown in FIG4 is similar and will not be described in detail here.

[0205] According to an embodiment of the present application, the present application also provides a communication device, a computer-readable storage medium and a computer program product.

[0206] like Figure 6 As shown, Figure 6 is a schematic diagram of the structure of the communication device provided by the present application. The communication device is intended for various forms of digital computers, such as laptop computers, desktop computers, workstations, personal digital assistants, vehicle-mounted terminals, and other suitable computers. The components shown herein, their connections and relationships, and their functions are merely examples and are not intended to limit the implementation of the present application described and / or required herein.

[0207] like Figure 6 As shown, the communication device includes: a processor 401 and a memory 402. The various components are connected to each other using different buses and can be installed on a common mainboard or in other ways as required. The processor can process instructions executed in the communication device.

[0208] The memory 402 is a non-transient computer-readable storage medium provided in the present application. The memory stores instructions executable by at least one processor to enable at least one processor to perform the crystal oscillator frequency deviation determination method provided in the present application. The non-transient computer-readable storage medium of the present application stores computer instructions, which are used to enable a computer to perform the crystal oscillator frequency deviation determination method provided in the present application.

[0209] The memory 402 is a non-transient computer-readable storage medium that can be used to store non-transient software programs, non-transient computer executable programs and modules, such as the program instructions / modules corresponding to the crystal oscillator frequency deviation determination method in the embodiment of the present application (for example, the attached Figure 5 The processor 401 executes various functional applications and data processing of the communication device by running the non-transient software programs, instructions and modules stored in the memory 402, that is, the crystal oscillator frequency deviation determination method in the above method embodiment is implemented.

[0210] At the same time, a computer-readable storage medium is provided, in which computer-executable instructions are stored. When the computer-executable instructions are executed by a processor, the method for determining the crystal oscillator frequency deviation of the above embodiment is implemented.

[0211] This embodiment further provides a computer product. When instructions in the computer product are executed by a processor of a communication device, the communication device can execute the crystal oscillator frequency deviation determination method of the above embodiment.

[0212] Those skilled in the art will readily come up with other implementations of the embodiments of the present application after considering the specification and practicing the invention disclosed herein. The present application is intended to cover any modifications, uses or adaptations of the embodiments of the present application, which follow the general principles of the embodiments of the present application and include common knowledge or customary technical means in the art that are not disclosed in the embodiments of the present application.

[0213] It should be understood that the embodiments of the present application are not limited to the precise structures described above and shown in the drawings, and various modifications and changes can be made without departing from the scope thereof. The scope of the embodiments of the present application is limited only by the appended claims.

Claims

1. A method for determining a crystal oscillator frequency deviation, characterized in that: include: Performing mixing processing on the low local oscillator carrier to generate a corresponding first mixing result; The low local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal; The theoretical signal is a downlink signal received when no Doppler frequency shift occurs; Performing mixing processing on the high local oscillator carrier to generate a corresponding second mixing result; The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal; The crystal oscillator frequency deviation is determined according to the first mixing result and the second mixing result.

2. The method according to claim 1, characterized in that The mixing process is performed on the low local oscillator carrier to generate a corresponding first mixing result, including: The low local oscillator carrier and the first actual signal are mixed and processed to generate a complex signal to generate a first in-phase orthogonal IQ complex signal; the first actual signal is a first downlink signal received when a Doppler frequency shift occurs; The first IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding first mixing result.

3. The method according to claim 2, characterized in that The mixing of the low local oscillator carrier and the first actual signal and complex signal generation processing to generate a first in-phase orthogonal IQ complex signal includes: Performing analog mixing processing on the low local oscillator carrier and the first actual signal to generate a first intermediate signal; Using a low-pass filter to perform low-pass filtering on the first intermediate signal to generate a second intermediate signal; The second intermediate signal is sampled by an analog-to-digital converter to generate a first IQ complex signal.

4. The method according to claim 2, characterized in that: The step of performing digital mixing processing and digital down-conversion processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding first mixing result includes: Performing digital mixing processing on the first IQ complex signal and the preset intermediate frequency signal to generate a corresponding third intermediate signal; The third intermediate signal is subjected to negative frequency filtering and down-sampling processing to generate a corresponding first mixing result.

5. The method according to claim 2, characterized in that: The mixing process is performed on the high local oscillator carrier to generate a corresponding second mixing result, including: The high local oscillator carrier and the second actual signal are mixed and processed to generate a complex signal to generate a second IQ complex signal; the second actual signal is a second downlink signal received when a Doppler frequency shift occurs; The second IQ complex signal and the preset intermediate frequency signal are digitally mixed and digitally down-converted to generate a corresponding second mixing result.

6. The method according to claim 5, characterized in that The mixing of the high local oscillator carrier and the second actual signal and complex signal generation processing to generate the second IQ complex signal includes: Performing analog mixing processing on the high local oscillator carrier and the second actual signal to generate a fourth intermediate signal; low-pass filtering the fourth intermediate signal using a low-pass filter to generate a fifth intermediate signal; The fifth intermediate signal is sampled by an analog-to-digital converter to generate a second IQ complex signal.

7. The method according to claim 5, characterized in that The step of performing digital mixing processing and digital down-conversion processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding second mixing result includes: Performing digital mixing processing on the second IQ complex signal and the preset intermediate frequency signal to generate a corresponding sixth intermediate signal; The sixth intermediate signal is subjected to negative frequency filtering and down-sampling processing to generate a corresponding second mixing result.

8. The method according to claim 5, characterized in that The first actual signal is the same as the second actual signal, or there is a preset time difference between the first actual signal and the second actual signal when they are received.

9. The method according to claim 1, characterized in that: The determining the crystal oscillator frequency deviation according to the first mixing result and the second mixing result includes: The first mixing result, the second mixing result and the preset intermediate frequency are input into a preset crystal oscillator frequency deviation calculation algorithm, and the crystal oscillator frequency deviation is determined using the preset crystal oscillator frequency deviation calculation algorithm; the preset intermediate frequency is the frequency of the preset intermediate frequency signal.

10. The method according to any one of claims 1 to 9, characterized in that: The method further comprises: Inputting the first mixing result, the second mixing result, the theoretical signal frequency and the preset intermediate frequency into a preset Doppler frequency deviation algorithm, and using the preset Doppler frequency deviation algorithm to determine the Doppler frequency deviation; the theoretical signal frequency is the frequency of the theoretical signal; The first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency are input into a preset crystal oscillator uncertainty algorithm, and the preset crystal oscillator uncertainty algorithm is used to determine the crystal oscillator uncertainty; the low local oscillator carrier frequency is the frequency of the low local oscillator carrier.

11. The method according to claim 10, characterized in that After inputting the first mixing result, the second mixing result, the low local oscillator carrier frequency and the preset intermediate frequency into a preset crystal oscillator uncertainty algorithm to determine the crystal oscillator uncertainty, the method further includes: Inputting the crystal oscillator uncertainty, Doppler frequency deviation, and theoretical signal frequency into a preset compensation algorithm, and using the preset compensation algorithm to generate an uplink compensation frequency; The uplink generated signal is frequency compensated according to the uplink compensation frequency.

12. A crystal oscillator frequency deviation determination device, characterized in that: include: A first frequency mixing module, used for performing frequency mixing processing on the low local oscillator carrier to generate a corresponding first frequency mixing result; The low local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal; The theoretical signal is a downlink signal received when no Doppler frequency shift occurs; A second frequency mixing module, used for performing frequency mixing processing on the high local oscillator carrier to generate a corresponding second frequency mixing result; The high local oscillator carrier is generated based on the received theoretical signal and the preset intermediate frequency signal; A determination module is used to determine a crystal oscillator frequency deviation according to the first mixing result and the second mixing result.

13. A communication device, characterized in that: include: Memory and processor; The memory stores computer-executable instructions; The processor executes the computer-executable instructions stored in the memory to implement the crystal oscillator frequency deviation determination method according to any one of claims 1 to 11.

14. A computer-readable storage medium, characterized in that: The computer-readable storage medium stores computer-executable instructions, and when the computer-executable instructions are executed by a processor, they are used to implement the crystal oscillator frequency deviation determination method according to any one of claims 1 to 11.

15. A computer program product comprising a computer program, characterized in that When the computer program is executed by a processor, the method for determining the crystal oscillator frequency deviation as claimed in any one of claims 1 to 11 is implemented.

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