A metrology device remote calibration method, apparatus, medium, and device

Abstract

The application discloses a kind of metering equipment remote calibration method, device, medium and equipment.Therein, method includes: according to the current characteristic of extracted current signal in monitoring period, loss index is calculated, and the phase shift of each harmonic is determined based on loss index;According to the ambient temperature and the ambient humidity in environment management period, environment gain coefficient is constructed;According to the fundamental wave amplitude of current signal in monitoring period and environment gain coefficient, current correction coefficient is constructed;According to current correction coefficient, each harmonic amplitude in next monitoring period is corrected, and according to the phase shift of each harmonic, each harmonic phase in next monitoring period is corrected, and the calibration current of next monitoring period is obtained.

Description

Technical Field

[0001] This invention relates to the field of power testing equipment technology, and more specifically, to a method, apparatus, medium, and equipment for remote calibration of metering equipment. Background Technology

[0002] The existing remote calibration technology for power testing equipment mainly relies on fixed-cycle compensation and linear temperature rise prediction models, which are difficult to adapt to complex operating conditions such as superposition of high-order harmonics (2kHz~20kHz) and sudden temperature changes (-10℃~50℃) under different calibration environments.

[0003] Specifically, during remote calibration of power metering equipment (such as instrument transformer calibrators), high-order harmonics can interfere with signal acquisition and error calculation accuracy. Traditional linear prediction models cannot dynamically match the core loss and phase shift characteristics under harmonic environments, leading to the accumulation of calibration errors over time. Furthermore, temperature and humidity compensation mechanisms based on empirical formulas exhibit lag in response when metering equipment faces metastable states such as approaching dew point or conductor condensation. Especially when the internal insulation material experiences micro-discharge due to sudden humidity changes, it can exacerbate time-varying errors in the internal measurement circuit, directly affecting the accuracy of remote calibration.

[0004] The essence of such technical defects lies in the fact that existing methods do not fully consider the dynamic characteristics of power testing equipment in multi-physics field (electromagnetic-thermal-humidity field) coupling environments. Therefore, it is urgent to establish a multi-physics field dynamic coupling highly robust calibration method suitable for the remote calibration needs of metrology equipment in order to solve the problem of calibration accuracy degradation under complex working conditions. Summary of the Invention

[0005] To address the shortcomings of existing technologies, this invention provides a method, apparatus, medium, and equipment for remote calibration of metrology equipment.

[0006] According to one aspect of the present invention, a remote calibration method for a measuring device is provided, comprising:

[0007] The loss index is calculated based on the current characteristics of the current signal extracted during the monitoring period, and the phase offset of each harmonic is determined based on the loss index.

[0008] An environmental gain coefficient is constructed based on the ambient temperature and humidity during the environmental management cycle.

[0009] Based on the fundamental amplitude of the current signal and the environmental gain coefficient within the monitoring period, a current correction coefficient is constructed.

[0010] The amplitude of each harmonic in the next monitoring cycle is corrected according to the current correction coefficient, and the phase of each harmonic in the next monitoring cycle is corrected according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

[0011] Optionally, a loss index is calculated based on the current characteristics of the extracted current signal within the monitoring period, including:

[0012] Acquire current signals during the detection period;

[0013] The amplitude values ​​of each harmonic of the current signal are extracted using the Fast Fourier Transform method;

[0014] Calculate the magnetic flux intensity based on the amplitude of each harmonic and the proportional coefficient of the transformer.

[0015] The loss index is calculated based on the magnetic flux density.

[0016] Optionally, the expression for calculating the loss index is:

[0017]

[0018] In the formula, P is the loss exponent, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, fn is the frequency exponent, fn=n×50Hz; Bn is the magnetic induction intensity of the nth harmonic.

[0019] Optionally, the phase shift of each harmonic is determined based on the loss exponent, including:

[0020] Extract the effective voltage value of the nth harmonic of the current signal;

[0021] Calculate the equivalent resistance of the nth harmonic based on the effective voltage value and the loss exponent;

[0022] Calculate the phase offset of the nth harmonic using the equivalent resistance, magnetizing inductance of the current transformer, and frequency index.

[0023] Optionally, the formula for calculating the equivalent resistance is:

[0024] Rn = Vn 2 / P

[0025] In the formula, Vn is the effective value of voltage; P is the loss exponent;

[0026] The expression for calculating the phase offset θn is:

[0027] θn=arctan(2×π×fn×L / Rn)

[0028] In the formula, θn is the nth harmonic offset; fn is the frequency exponent; and L is the magnetizing inductance of the transformer.

[0029] Optionally, an environmental gain coefficient is constructed based on the ambient temperature and humidity during the monitoring period, including:

[0030] Calculate the ambient temperature threshold based on ambient temperature and humidity;

[0031] The water vapor state is determined based on the ambient temperature threshold and ambient humidity, and an environmental gain coefficient is constructed based on the water vapor state.

[0032] Optionally, the calculation expression for the ambient temperature threshold is:

[0033]

[0034] In the formula, Y is the ambient temperature threshold, β1 is the temperature offset coefficient, β2 is the temperature empirical constant; t is the ambient temperature, and s is the ambient humidity.

[0035] Optionally, the water vapor state is determined based on the ambient temperature threshold and ambient humidity, and an environmental gain coefficient is constructed based on the water vapor state, including:

[0036] If the ambient temperature is less than or equal to T+2 and the ambient humidity is greater than or equal to the preset humidity threshold s1, the water vapor state is determined to be an abnormal state, and the environmental gain coefficient is constructed as [1+γ×(s-s1)], where γ is an adjustment factor. Otherwise, the water vapor state is determined to be a normal state, and the environmental gain coefficient is constructed as 1.

[0037] Optionally, it also includes updating the environmental gain coefficient based on the change in the protection ring capacitance during the environmental management cycle.

[0038] Optionally, the environmental gain coefficient is updated based on the change in the protection ring capacitance during the environmental management cycle, including:

[0039] The rate of change of the protective ring capacitance BH is calculated based on the protective ring capacitance D1 collected in the environmental management cycle and the protective ring capacitance D2 collected in the previous environmental management cycle, where Δt is the duration of the environmental management cycle.

[0040] If the change rate of the protective ring capacitance BH is greater than the preset change rate threshold b0, then the environmental gain coefficient is updated to {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is the update coefficient and HK is the environmental gain coefficient before the update; otherwise, the environmental gain coefficient is not updated.

[0041] Optionally, a current correction coefficient is constructed based on the fundamental amplitude of the current signal and the environmental gain coefficient within the monitoring period, including:

[0042] The current correction weighting factor is determined based on the fundamental amplitude of the current signal within the monitoring period;

[0043] The current correction coefficient is constructed based on the current correction weight shadow and the environmental gain coefficient.

[0044] Optionally, the expression for the current correction weighting factor is:

[0045]

[0046] In the formula, W is the current correction weighting factor, F1 is the fundamental amplitude during the monitoring period, and Fn is the amplitude of the nth harmonic.

[0047] Optionally, current correction coefficients are constructed based on the current correction weight shadow and the environmental gain coefficient, including:

[0048] When the current correction weight factor is less than or equal to the compensation threshold r0, the current correction coefficient is constructed as [z1×(1-0.1×W)×environmental gain coefficient], otherwise the current correction coefficient is constructed as [z2×(1-0.1×W)×environmental gain coefficient], where z1 is the first compensation factor and z2 is the second compensation factor.

[0049] Optionally, the amplitude of each harmonic of the calibration current is Fnjj = Fnj × current correction coefficient, where Fnj is the measured value of the nth harmonic amplitude in the next monitoring cycle;

[0050] Phase of each harmonic of the calibration current θn is the measured value of the nth harmonic phase in the next monitoring cycle; θn is the nth harmonic offset.

[0051] According to another aspect of the present invention, a remote calibration device for metrology equipment is provided, comprising:

[0052] The calculation module is used to calculate the loss index based on the current characteristics of the current signal extracted within the monitoring period, and to determine the phase offset of each harmonic based on the loss index.

[0053] The first construction module is used to construct the environmental gain coefficient based on the ambient temperature and humidity during the environmental management cycle.

[0054] The second construction module is used to construct the current correction coefficient based on the fundamental amplitude of the current signal and the environmental gain coefficient within the monitoring period.

[0055] The calibration module is used to correct the amplitude of each harmonic in the next monitoring cycle according to the current correction coefficient, and to correct the phase of each harmonic in the next monitoring cycle according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

[0056] According to another aspect of the present invention, a computer-readable storage medium is provided, the storage medium storing a computer program for performing the methods described in any of the above aspects of the present invention.

[0057] According to another aspect of the present invention, an electronic device is provided, the electronic device comprising: a processor; a memory for storing executable instructions of the processor; the processor being configured to read the executable instructions from the memory and execute the instructions to implement the method described in any of the preceding aspects of the present invention.

[0058] Therefore, this invention achieves precise compensation for the amplitude and phase of high-frequency signals across the entire frequency band by analyzing harmonic energy loss and the nonlinear transmission law of the iron core. Combined with a composite sensing mechanism of temperature, humidity, and protective ring status, a predictive adjustment system for the environmental gain coefficient is constructed, effectively overcoming the inherent bias of the linear temperature drift model. Based on a closed-loop hierarchical verification architecture generated by dynamic weights, it balances rapid calibration response with long-term error stability control. Compared with traditional methods, this invention systematically solves the problems of metering distortion induced by harmonic group distortion and alternating humidity and heat, significantly improving the reliability of energy efficiency metering and the efficiency of equipment lifecycle management under complex operating conditions. Attached Figure Description

[0059] Exemplary embodiments of the present invention can be more fully understood by referring to the following figures:

[0060] Figure 1 This is a flowchart illustrating a remote calibration method for metrology equipment provided in an exemplary embodiment of the present invention.

[0061] Figure 2 This is a schematic diagram of the structure of a remote calibration device for metrology equipment provided in an exemplary embodiment of the present invention;

[0062] Figure 3 This is the structure of an electronic device provided in an exemplary embodiment of the present invention. Detailed Implementation

[0063] Hereinafter, exemplary embodiments according to the present invention will be described in detail with reference to the accompanying drawings. Obviously, the described embodiments are merely some embodiments of the present invention, and not all embodiments of the present invention. It should be understood that the present invention is not limited to the exemplary embodiments described herein.

[0064] It should be noted that, unless otherwise specifically stated, the relative arrangement, numerical expressions, and values ​​of the components and steps described in these embodiments do not limit the scope of the invention.

[0065] Those skilled in the art will understand that the terms "first," "second," etc., in the embodiments of the present invention are only used to distinguish different steps, devices, or modules, and do not represent any specific technical meaning, nor do they indicate a necessary logical order between them.

[0066] It should also be understood that in the embodiments of the present invention, "multiple" can refer to two or more, and "at least one" can refer to one, two or more.

[0067] It should also be understood that any component, data or structure mentioned in the embodiments of the present invention can generally be understood as one or more unless explicitly defined or given contrary instructions in the context.

[0068] Furthermore, the term "and / or" in this invention is merely a description of the relationship between related objects, indicating that three relationships can exist. For example, A and / or B can represent: A existing alone, A and B existing simultaneously, or B existing alone. Additionally, the character " / " in this invention generally indicates that the preceding and following related objects have an "or" relationship.

[0069] It should also be understood that the description of the various embodiments in this invention emphasizes the differences between the various embodiments, and the similarities or similarities can be referred to each other. For the sake of brevity, they will not be described in detail.

[0070] At the same time, it should be understood that, for ease of description, the dimensions of the various parts shown in the accompanying drawings are not drawn according to actual scale.

[0071] The following description of at least one exemplary embodiment is merely illustrative and is in no way intended to limit the invention or its application or use.

[0072] Techniques, methods, and equipment known to those skilled in the art may not be discussed in detail, but where appropriate, they should be considered part of the specification.

[0073] It should be noted that similar labels and letters in the following figures indicate similar items; therefore, once an item is defined in one figure, it does not need to be discussed further in subsequent figures.

[0074] The embodiments of this invention can be applied to electronic devices such as terminal devices, computer systems, and servers, and can operate together with a wide range of other general-purpose or special-purpose computing system environments or configurations. Well-known examples of terminal devices, computing systems, environments, and / or configurations suitable for use with electronic devices such as terminal devices, computer systems, and servers include, but are not limited to: personal computer systems, server computer systems, thin clients, thick clients, handheld or laptop devices, microprocessor-based systems, set-top boxes, programmable consumer electronics, network PCs, minicomputer systems, mainframe computer systems, and distributed cloud computing environments including any of the above systems, etc.

[0075] Electronic devices such as terminal devices, computer systems, and servers can be described in the general context of computer system executable instructions (such as program modules) executed by a computer system. Typically, program modules can include routines, programs, object programs, components, logic, data structures, etc., which perform specific tasks or implement specific abstract data types. Computer systems / servers can be implemented in distributed cloud computing environments, where tasks are executed by remote processing devices linked through communication networks. In distributed cloud computing environments, program modules can reside on local or remote computing system storage media, including storage devices.

[0076] Exemplary methods

[0077] Figure 1 This is a schematic flowchart of a remote calibration method for metrology equipment provided in an exemplary embodiment of the present invention. This embodiment can be applied to electronic devices, such as... Figure 1 As shown, the remote calibration method 100 for metrology equipment includes the following steps:

[0078] Step 101: Calculate the loss index based on the current characteristics of the current signal extracted during the monitoring period, and determine the phase offset of each harmonic based on the loss index.

[0079] Step 102: Construct an environmental gain coefficient based on the ambient temperature and humidity during the environmental management cycle;

[0080] Step 103: Construct current correction coefficients based on the fundamental amplitude of the current signal and the environmental gain coefficient within the monitoring period;

[0081] Step 104: Correct the amplitude of each harmonic in the next monitoring cycle according to the current correction coefficient, and correct the phase of each harmonic in the next monitoring cycle according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

[0082] This embodiment proposes a remote calibration method based on harmonic iron loss-phase coupling modeling and multi-parameter dynamic compensation for distributed photovoltaic metering scenarios with high-order harmonic superposition and strong environmental disturbances. Specifically, it includes:

[0083] Step S101: Acquire the target's current and voltage signals.

[0084] Specifically, the target described in this embodiment is a current transformer calibrator. Those skilled in the art can set the target as a power testing-related device with metering function.

[0085] For example, in this embodiment, an AD7606-8 channel 16-bit ADC chip can be used to simultaneously acquire three-phase voltage and current. The sampling rate is fixed at 10kHz to ensure the capture of harmonics below the 50th order. The fundamental +2 to 50th harmonics are decomposed by the FFT module of the ADSP-BF707 processor. In this embodiment, no specific limitation is made on the data acquisition method. Those skilled in the art can set it freely according to their needs.

[0086] Step S102: Extract current characteristics based on the current signal within the monitoring period to determine the loss index, and determine the phase offset of each harmonic based on the loss index.

[0087] Specifically, by quantifying the impact of harmonic losses on core performance and accurately modeling the phase lag effect of each harmonic, the nonlinear error of the transformer under high-frequency operating conditions can be specifically corrected, fundamentally improving the measurement integrity of harmonic components. This method solves the problem of the crude compensation defect in the traditional scheme that simplifies harmonics to amplitude superposition.

[0088] Step S102 includes:

[0089] Step S201: Extract current characteristics based on the current signal within the monitoring period to determine the loss index.

[0090] Specifically, the amplitudes of each harmonic of the current signal within the monitoring period are extracted using the Fast Fourier Transform, and the amplitude of the nth harmonic is denoted as Fn. The product of Fn and the proportional coefficient h of the transformer is taken as the magnetic flux density corresponding to the amplitude of the nth harmonic, and the loss exponent is calculated. The expression for the loss exponent is as follows:

[0091]

[0092] In the formula, P is the loss exponent, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, and fn is the frequency exponent, fn=n×50Hz.

[0093] Specifically, by modeling the coupling of harmonic magnetic induction intensity and frequency parameters, the influence of iron loss on transmission characteristics is quantitatively restored, providing a clear physical basis for compensation strategies and overcoming the limitations of empirical formulas that rely on measured data.

[0094] For example, in this embodiment, the monitoring period can be set to 1 minute. This embodiment does not specifically limit the setting of the monitoring period, and those skilled in the art can set it freely according to their needs.

[0095] For example, in this embodiment, a fast Fourier transform can be used to perform spectrum analysis on the sampled signal, directly locate the amplitude of the harmonic frequency point from the spectrum, and divide the read harmonic amplitude by the square root of 2 to obtain the effective value voltage of the harmonic. For example, in this embodiment, no specific limitation is made on the acquisition method of each harmonic amplitude and its corresponding effective value voltage. Those skilled in the art can set it freely according to their needs.

[0096] For example, in this embodiment, the hysteresis loss coefficient can be set to 3.2 × 10⁻⁶. -5 W / (T 1.6 The eddy current loss coefficient can be set to 8.9 × 10⁻⁶ Hz. -7 W / (T 2 ·Hz 2 The mutual inductance ratio coefficient can be set to 10. -3 In this embodiment, the hysteresis loss coefficient, eddy current loss coefficient, and mutual inductance ratio coefficient can be obtained interactively, and those skilled in the art can set them according to the nameplate parameters of the mutual inductor.

[0097] Step S202: Determine the phase offset of each harmonic based on the loss index.

[0098] Specifically, the effective voltage value of the nth harmonic is extracted as Vn, and the equivalent resistance Rn corresponding to the nth harmonic is calculated based on Vn and the loss index P. The expression for the equivalent resistance Rn corresponding to the nth harmonic is: Rn = Vn 2 / P;

[0099] The equivalent resistance Rn corresponding to the nth harmonic, the magnetizing inductance L of the current transformer, and the frequency index fn are fused to determine the phase shift of the nth harmonic. The expression for the phase shift of the nth harmonic is:

[0100] θn=arctan(2×π×fn×L / Rn).

[0101] Specifically, the phase lag angle is inverted based on the equivalent resistance and inductance characteristics, revealing the analytical relationship between the core material characteristics and the measurement error. This gives the phase calibration parameters clear boundary condition constraints, avoiding the divergence problem caused by frequency extrapolation in traditional phase compensation.

[0102] For example, this embodiment does not specifically limit the method of obtaining the excitation inductance of the current transformer. Those skilled in the art can set it freely according to their needs, such as obtaining the excitation inductance of the current transformer through interaction.

[0103] Step S103: Calculate the ambient temperature threshold based on the ambient temperature and humidity collected during the environmental management cycle, and determine the water vapor state based on the ambient temperature threshold and ambient humidity to construct an environmental gain coefficient. The ambient temperature is the temperature inside the meter box, and the ambient humidity is the ambient humidity where the meter box is located.

[0104] Specifically, the ambient temperature threshold is calculated based on the ambient temperature t and ambient humidity s collected during the environmental management cycle. The expression for the ambient temperature threshold is:

[0105]

[0106] In the formula, Y is the ambient temperature threshold, β1 is the temperature offset coefficient, and β2 is the empirical temperature constant.

[0107] When the ambient temperature t is less than or equal to (ambient temperature threshold Y+2) and the ambient humidity s is greater than or equal to the humidity threshold s1, the water vapor state of the current management cycle is determined to be an abnormal state, and an environmental gain coefficient of [1+γ×(s-s1)] is constructed, where γ is an adjustment factor. Conversely, when the ambient temperature t is less than or equal to (ambient temperature threshold Y+2) and the ambient humidity s is greater than or equal to the humidity threshold s1, the water vapor state of the current management cycle is determined to be a normal state, and an environmental gain coefficient of 1 is constructed.

[0108] Specifically, by introducing a dew point temperature threshold mechanism, the traditional single temperature and humidity monitoring is upgraded to a joint prediction system for the environmental safety domain. This mechanism can dynamically identify the combined risks of temperature and humidity within the instrument box and construct an environmental gain coefficient matrix based on adjustment factors, achieving hierarchical control of compensation intensity. This method not only inhibits the insulation degradation process caused by humidity penetration but also effectively reduces high-frequency oscillation errors caused by environmental abrupt changes by addressing the nonlinear compensation of reference voltage temperature drift under metastable operating conditions. Furthermore, through time-sequential control of the environmental management cycle, the update of the gain coefficient achieves both rapid response and parameter stability.

[0109] For example, in this embodiment, the environmental management cycle can be set to 0.25h. This embodiment does not specifically limit the setting of the environmental management cycle, and those skilled in the art can set it freely according to their needs.

[0110] For example, in this embodiment, the temperature offset coefficient can be set to 237.3, the temperature empirical constant can be set to 17.27, the humidity threshold can be set to 75, and the adjustment factor can be set to 0.003. This embodiment does not specifically limit the above settings, and those skilled in the art can set them freely according to their needs.

[0111] For example, in this embodiment, the ambient temperature can be obtained by a temperature sensor and the ambient humidity can be obtained by a humidity sensor. This embodiment does not specifically limit the method of obtaining the ambient temperature and ambient humidity, and those skilled in the art can set them freely according to their needs.

[0112] Specifically, in this embodiment, the unit of ambient temperature is ℃ and the unit of ambient humidity is %. When calculating them, only their numerical values ​​are considered, not their units. Ambient temperature and ambient humidity are collected at the beginning of the environmental management cycle, and the environmental gain coefficient is also constructed at the beginning of the environmental management cycle.

[0113] Step S104: Determine the change state of the protective ring capacitance based on the protective ring capacitance collected during the environmental management cycle, and update the environmental gain coefficient based on the change state of the protective ring capacitance. The protective ring is a ring conductor wrapped around the outer layer of the measurement circuit, and the protective ring capacitance refers to the parasitic capacitance between the protective ring and the adjacent conductor structure in the target.

[0114] Specifically, the protection ring capacitance D1 collected in the environmental management cycle is compared with the protection ring capacitance D2 collected in the previous environmental management cycle to calculate the protection ring capacitance change rate BH, BH=|D1-D2| / (D2×△t), where △t is the duration of the environmental management cycle. If BH is greater than the change rate threshold b0, the environmental gain coefficient is updated to {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is the update coefficient. If BH is less than or equal to the change rate threshold b0, the environmental gain coefficient is not updated, and HK is the environmental gain coefficient before the update.

[0115] Specifically, by monitoring the dynamic changes in parasitic capacitance between the protective ring and adjacent conductors, this method indirectly senses capacitance anomalies caused by external pollution, mechanical deformation, or contact oxidation. This approach overcomes the limitation of conventional environmental sensors, which can only detect macroscopic temperature and humidity but cannot capture microscopic changes in the conductor surface. It is particularly suitable for early warning of latent interference caused by dust accumulation and corrosion in long-term outdoor equipment. Combined with gradient threshold discrimination of capacitance change rate, it can accurately identify slow degradation and abrupt voltage change scenarios. A segmented gain correction strategy is then employed: logarithmic smoothing compensation is applied to slow offsets to maintain stability, while rapid response suppression is applied to abrupt interference to block the chain propagation of errors, significantly improving the robustness of the metering system in complex polluted environments.

[0116] For example, in this embodiment, the change rate threshold can be set to 0.1% / h, the update coefficient can be set to 0.12, and the update coefficient can be set to 0.05. This embodiment does not specifically limit the above settings, and those skilled in the art can set them freely according to their needs.

[0117] For example, in this embodiment, the capacitance of the protective ring can be collected using a capacitance measurement chip.

[0118] Step S105: Determine the current correction coefficient based on the extraction results of the current characteristics within the monitoring period and the environmental gain coefficient, and correct the amplitude and phase of each harmonic based on the current correction coefficient and the phase offset of each harmonic.

[0119] Step S105 includes:

[0120] Step S501: Determine the current correction weight factor based on the extraction results of current characteristics within the monitoring period, and construct the current correction coefficient based on the current correction weight factor and the environmental gain coefficient.

[0121] Specifically, the expression for the current correction weighting factor is:

[0122]

[0123] In the formula, W is the current correction weighting factor, and F1 is the fundamental amplitude during the monitoring period;

[0124] The current correction coefficient is constructed based on the current correction weight factor W. When the current correction weight factor is less than or equal to the compensation threshold r0, the current correction coefficient is set to [z1×(1-0.1×W)×environmental gain coefficient], and when the current correction weight factor is greater than the compensation threshold r0, the current correction coefficient is set to [z2×(1-0.1×W)×environmental gain coefficient];

[0125] Where z1 is the first compensation factor and z2 is the second compensation factor.

[0126] Specifically, a segmented correction coefficient is constructed by combining environmental gain and harmonic characteristics, which allows for adaptive adjustment of the compensation intensity under different operating conditions. This ensures both the smoothness of measurement under steady-state conditions and the ability to quickly converge errors during transient disturbances.

[0127] For example, in this embodiment, the compensation threshold can be set to 0.1, the first compensation factor can be set to 0.98, and the second compensation factor can be set to 0.95. In this embodiment, the above settings are not specifically limited, and those skilled in the art can set them freely according to their needs.

[0128] Step S502: Correct the amplitude of each harmonic in the next monitoring cycle according to the current correction coefficient, and correct the phase of each harmonic in the next monitoring cycle according to the phase offset of each harmonic.

[0129] Specifically, the amplitude of the nth harmonic in the next monitoring cycle is corrected to Fnjj, where Fnjj = Fnj × current correction coefficient, and Fnj is the measured value of the amplitude of the nth harmonic in the next monitoring cycle.

[0130] Correct the nth harmonic phase for the next monitoring cycle. This is the measured value of the nth harmonic phase for the next monitoring cycle.

[0131] Specifically, through a closed-loop recursive mechanism of "measurement-feature extraction-parameter update", dynamic tracking of error correction is achieved, ensuring parameter continuity across monitoring cycles and significantly reducing periodic error fluctuations caused by calibration parameter lag.

[0132] Specifically, in this embodiment, the first harmonic is the fundamental frequency.

[0133] Therefore, this invention achieves precise compensation for the amplitude and phase of high-frequency signals across the entire frequency band by analyzing harmonic energy loss and the nonlinear transmission law of the iron core. Combined with a composite sensing mechanism of temperature, humidity, and protective ring status, a predictive adjustment system for the environmental gain coefficient is constructed, effectively overcoming the inherent bias of the linear temperature drift model. Based on a closed-loop hierarchical verification architecture generated by dynamic weights, it balances rapid calibration response with long-term error stability control. Compared with traditional methods, this invention systematically solves the problems of metering distortion induced by harmonic group distortion and alternating humidity and heat, significantly improving the reliability of energy efficiency metering and the efficiency of equipment lifecycle management under complex operating conditions.

[0134] Exemplary device

[0135] Figure 2 This is a schematic diagram of the structure of a remote calibration device for metrology equipment provided in an exemplary embodiment of the present invention. For example... Figure 2 As shown, the device 200 includes:

[0136] The calculation module 210 is used to calculate the loss index based on the current characteristics of the current signal extracted during the monitoring period, and to determine the phase offset of each harmonic based on the loss index.

[0137] The first construction module 220 is used to construct an environmental gain coefficient based on the ambient temperature and humidity during the environmental management cycle.

[0138] The second construction module 230 is used to construct the current correction coefficient based on the fundamental amplitude of the current signal and the environmental gain coefficient within the monitoring period.

[0139] The calibration module 240 is used to correct the amplitude of each harmonic in the next monitoring cycle according to the current correction coefficient, and to correct the phase of each harmonic in the next monitoring cycle according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

[0140] Optionally, the calculation module 210 calculates the loss index based on the current characteristics of the extracted current signal within the monitoring period, including:

[0141] The acquisition submodule is used to acquire the current signal during the detection period;

[0142] The extraction submodule is used to extract the amplitude values ​​of each harmonic of the current signal using the fast Fourier transform method;

[0143] The first calculation submodule is used to calculate the magnetic induction intensity based on the amplitude of each harmonic and the proportional coefficient of the transformer.

[0144] The second calculation submodule is used to calculate the loss index based on the magnetic induction intensity.

[0145] Optionally, the expression for calculating the loss index is:

[0146]

[0147] In the formula, P is the loss exponent, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, fn is the frequency exponent, fn=n×50Hz; Bn is the magnetic induction intensity of the nth harmonic.

[0148] Optionally, the calculation module 210 determines the phase shift of each harmonic based on the loss exponent, including:

[0149] Extract the effective voltage value of the nth harmonic of the current signal;

[0150] Calculate the equivalent resistance of the nth harmonic based on the effective voltage value and the loss exponent;

[0151] Calculate the phase offset of the nth harmonic using the equivalent resistance, magnetizing inductance of the current transformer, and frequency index.

[0152] Optionally, the formula for calculating the equivalent resistance is:

[0153] Rn = Vn 2 / P

[0154] In the formula, Vn is the effective value of voltage; P is the loss exponent;

[0155] The expression for calculating the phase offset θn is:

[0156] θn=arctan(2×π×fn×L / Rn)

[0157] In the formula, θn is the nth harmonic offset; fn is the frequency exponent; and L is the magnetizing inductance of the transformer.

[0158] Optionally, the first building module 220 includes:

[0159] Calculate the ambient temperature threshold based on ambient temperature and humidity;

[0160] The water vapor state is determined based on the ambient temperature threshold and ambient humidity, and an environmental gain coefficient is constructed based on the water vapor state.

[0161] Optionally, the calculation expression for the ambient temperature threshold is:

[0162]

[0163] In the formula, Y is the ambient temperature threshold, β1 is the temperature offset coefficient, β2 is the temperature empirical constant; t is the ambient temperature, and s is the ambient humidity.

[0164] Optionally, the water vapor state is determined based on the ambient temperature threshold and ambient humidity, and an environmental gain coefficient is constructed based on the water vapor state, including:

[0165] If the ambient temperature is less than or equal to T+2 and the ambient humidity is greater than or equal to the preset humidity threshold s1, the water vapor state is determined to be an abnormal state, and the environmental gain coefficient is constructed as [1+γ×(s-s1)], where γ is an adjustment factor. Otherwise, the water vapor state is determined to be a normal state, and the environmental gain coefficient is constructed as 1.

[0166] Optionally, the device 200 further includes an update module for updating the environmental gain coefficient based on the change in the protection ring capacitance during the environmental management cycle.

[0167] Optionally, the update module includes:

[0168] The rate of change of the protective ring capacitance BH is calculated based on the protective ring capacitance D1 collected in the environmental management cycle and the protective ring capacitance D2 collected in the previous environmental management cycle, where Δt is the duration of the environmental management cycle.

[0169] If the change rate of the protective ring capacitance BH is greater than the preset change rate threshold b0, then the environmental gain coefficient is updated to {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is the update coefficient and HK is the environmental gain coefficient before the update; otherwise, the environmental gain coefficient is not updated.

[0170] Optionally, the second building module 230 includes:

[0171] The current correction weighting factor is determined based on the fundamental amplitude of the current signal within the monitoring period;

[0172] The current correction coefficient is constructed based on the current correction weight shadow and the environmental gain coefficient.

[0173] Optionally, the expression for the current correction weighting factor is:

[0174]

[0175] In the formula, W is the current correction weighting factor, F1 is the fundamental amplitude during the monitoring period, and Fn is the amplitude of the nth harmonic.

[0176] Optionally, current correction coefficients are constructed based on the current correction weight shadow and the environmental gain coefficient, including:

[0177] When the current correction weight factor is less than or equal to the compensation threshold r0, the current correction coefficient is constructed as [z1×(1-0.1×W)×environmental gain coefficient], otherwise the current correction coefficient is constructed as [z2×(1-0.1×W)×environmental gain coefficient], where z1 is the first compensation factor and z2 is the second compensation factor.

[0178] Optionally, the amplitude of each harmonic of the calibration current is Fnjj = Fnj × current correction coefficient, where Fnj is the measured value of the nth harmonic amplitude in the next monitoring cycle;

[0179] Phase of each harmonic of the calibration current θn is the measured value of the nth harmonic phase in the next monitoring cycle; θn is the nth harmonic offset.

[0180] Exemplary electronic devices

[0181] Figure 3 This is the structure of an electronic device provided in an exemplary embodiment of the present invention. For example... Figure 3 As shown, the electronic device 30 includes one or more processors 31 and memory 32.

[0182] The processor 31 may be a central processing unit (CPU) or other form of processing unit with data processing and / or instruction execution capabilities, and may control other components in the electronic device to perform desired functions.

[0183] The memory 32 may include one or more computer program products, which may include various forms of computer-readable storage media, such as volatile memory and / or non-volatile memory. The volatile memory may include, for example, random access memory (RAM) and / or cache memory. The non-volatile memory may include, for example, read-only memory (ROM), hard disk, flash memory, etc. One or more computer program instructions may be stored on the computer-readable storage medium, and the processor 31 may execute the program instructions to implement the methods of the software programs of the various embodiments of the present invention described above, and / or other desired functions. In one example, the electronic device may also include an input device 33 and an output device 34, these components being interconnected via a bus system and / or other forms of connection mechanisms (not shown).

[0184] In addition, the input device 33 may also include, for example, a keyboard, a mouse, etc.

[0185] The output device 34 can output various information to the outside. The output device 34 may include, for example, a display, a speaker, a printer, and a communication network and its connected remote output devices, etc.

[0186] Of course, for the sake of simplicity, Figure 3 Only some of the components of this electronic device relevant to the present invention are shown, omitting components such as buses, input / output interfaces, etc. In addition, the electronic device may include any other suitable components depending on the specific application.

[0187] Exemplary computer program products and computer-readable storage media

[0188] In addition to the methods and apparatus described above, embodiments of the present invention may also be computer program products, which include computer program instructions that, when executed by a processor, cause the processor to perform the steps in the methods according to various embodiments of the present invention described in the "Exemplary Methods" section above.

[0189] The computer program product can be written in any combination of one or more programming languages ​​to perform the operations of the embodiments of the present invention. The programming languages ​​include object-oriented programming languages ​​such as Java and C++, as well as conventional procedural programming languages ​​such as C or similar languages. The program code can be executed entirely on the user's computing device, partially on the user's computing device, as a standalone software package, partially on the user's computing device and partially on a remote computing device, or entirely on a remote computing device or server.

[0190] Furthermore, embodiments of the present invention may also be computer-readable storage media storing computer program instructions thereon, which, when executed by a processor, cause the processor to perform the steps of the methods according to various embodiments of the present invention described in the "Exemplary Methods" section above.

[0191] The computer-readable storage medium may be any combination of one or more readable media. A readable medium may be a readable signal medium or a readable storage medium. A readable storage medium may be, for example, an electrical, magnetic, optical, electromagnetic, infrared, or semiconductor system, device, or any combination thereof. More specific examples (a non-exhaustive list) of readable storage media include: an electrical connection having one or more wires, a portable disk, a hard disk, random access memory (RAM), read-only memory (ROM), erasable programmable read-only memory (EPROM or flash memory), optical fiber, portable compact disk read-only memory (CD-ROM), optical storage device, magnetic storage device, or any suitable combination thereof.

[0192] The basic principles of the present invention have been described above with reference to specific embodiments. However, it should be noted that the advantages, benefits, and effects mentioned in the present invention are merely examples and not limitations, and should not be considered as essential features of each embodiment of the present invention. Furthermore, the specific details disclosed above are for illustrative and facilitative purposes only, and are not limitations. These details do not limit the present invention to the necessity of employing the aforementioned specific details.

[0193] The various embodiments in this specification are described in a progressive manner, with each embodiment focusing on its differences from other embodiments. Similar or identical parts between embodiments can be referred to interchangeably. For system embodiments, since they largely correspond to method embodiments, the description is relatively simple; relevant parts can be referred to the descriptions in the method embodiments.

[0194] The block diagrams of devices, systems, devices, and systems involved in this invention are merely illustrative examples and are not intended to require or imply that they must be connected, arranged, or configured in the manner shown in the block diagrams. As those skilled in the art will recognize, these devices, systems, devices, and systems can be connected, arranged, and configured in any manner. Words such as “comprising,” “including,” “having,” etc., are open-ended terms meaning “including but not limited to,” and are used interchangeably with them. The terms “or” and “and” as used herein refer to the terms “and / or,” and are used interchangeably with them unless the context clearly indicates otherwise. The term “such as” as used herein refers to the phrase “such as but not limited to,” and is used interchangeably with it.

[0195] The methods and systems of the present invention may be implemented in many ways. For example, they may be implemented by software, hardware, firmware, or any combination of software, hardware, and firmware. The above-described order of steps for the methods is for illustrative purposes only, and the steps of the methods of the present invention are not limited to the order specifically described above unless otherwise specifically stated. Furthermore, in some embodiments, the present invention may also be implemented as a program recorded on a recording medium, the program comprising machine-readable instructions for implementing the methods according to the present invention. Thus, the present invention also covers recording media storing programs for performing the methods according to the present invention.

[0196] It should also be noted that in the systems, apparatus, and methods of the present invention, the components or steps can be disassembled and / or recombined. These disassemblies and / or recombinations should be considered equivalents of the present invention. The above description of the disclosed aspects is provided to enable any person skilled in the art to make or use the invention. Various modifications to these aspects will be readily apparent to those skilled in the art, and the general principles defined herein can be applied to other aspects without departing from the scope of the invention. Therefore, the invention is not intended to be limited to the aspects shown herein, but rather to be carried out within the widest scope consistent with the principles and novel features disclosed herein.

[0197] The above description has been given for purposes of illustration and description. Furthermore, this description is not intended to limit the embodiments of the invention to the forms disclosed herein. Although numerous exemplary aspects and embodiments have been discussed above, those skilled in the art will recognize certain variations, modifications, alterations, additions, and sub-combinations thereof.

Claims

1. A method for remote calibration of measuring equipment, characterized in that, include: The loss index is calculated based on the current characteristics of the current signal extracted during the monitoring period, and the phase offset of each harmonic is determined based on the loss index. An environmental gain coefficient is constructed based on the ambient temperature and humidity during the environmental management cycle. Based on the fundamental amplitude of the current signal during the monitoring period and the environmental gain coefficient, a current correction coefficient is constructed. The amplitude of each harmonic in the next monitoring cycle is corrected according to the current correction coefficient, and the phase of each harmonic in the next monitoring cycle is corrected according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle. The loss index is calculated based on the current characteristics of the extracted current signal within the monitoring period, including: Acquire current signals during the detection period; The amplitude values ​​of each harmonic of the current signal are extracted using the Fast Fourier Transform method; Calculate the magnetic flux intensity based on the amplitude of each harmonic and the proportional coefficient of the transformer. The loss index is calculated based on the magnetic flux density. The expression for calculating the loss index is as follows: In the formula, P The loss index K 1 represents the hysteresis loss coefficient. K 2 represents the eddy current loss coefficient. fn For frequency index, fn = n ×50Hz; Bn for n The magnetic flux density of the subharmonic; The phase shift of each harmonic is determined based on the loss exponent, including: Extract the effective voltage value of the nth harmonic of the current signal; The equivalent resistance of the nth harmonic is calculated based on the effective voltage value and the loss exponent. Calculate the phase offset of the nth harmonic using the equivalent resistance, magnetizing inductance of the current transformer, and frequency index. The formula for calculating the equivalent resistance is: Rn=Vn 2 / P In the formula, Vn is the effective value of voltage; P is the loss exponent; The expression for calculating the phase offset θn is: θn=arctan(2×π× fn ×L / Rn) In the formula, θn is the nth harmonic offset; fn It is the frequency index; L It is the magnetizing inductance of the current transformer.

2. The method according to claim 1, characterized in that, Based on the ambient temperature and humidity during the monitoring period, an environmental gain coefficient is constructed, including: Calculate the ambient temperature threshold based on the ambient temperature and the ambient humidity; The water vapor state is determined based on the ambient temperature threshold and the ambient humidity, and the ambient gain coefficient is constructed based on the water vapor state.

3. The method according to claim 2, characterized in that, The calculation expression for the ambient temperature threshold is as follows: In the formula, Y β1 is the ambient temperature threshold, β2 is the temperature offset coefficient, and β2 is the empirical temperature constant. t s represents ambient temperature, and s represents ambient humidity.

4. The method according to claim 3, characterized in that, The water vapor state is determined based on the ambient temperature threshold and the ambient humidity, and the environmental gain coefficient is constructed based on the water vapor state, including: If the ambient temperature is less than or equal to T+2 and the ambient humidity is greater than or equal to a preset humidity threshold s1, the water vapor state is determined to be an abnormal state, and an environmental gain coefficient of [1+γ×(s-s1)] is constructed, where γ is an adjustment factor; otherwise, the water vapor state is determined to be a normal state, and an environmental gain coefficient of 1 is constructed.

5. The method according to claim 1, characterized in that, Also includes: The environmental gain coefficient is updated based on the change in the protection ring capacitance during the environmental management cycle.

6. The method according to claim 5, characterized in that, The environmental gain coefficient is updated based on the change in the protection ring capacitance during the environmental management cycle, including: The rate of change of the protective ring capacitance BH is calculated based on the protective ring capacitance D1 collected in the environmental management cycle and the protective ring capacitance D2 collected in the previous environmental management cycle, where Δt is the duration of the environmental management cycle. If the change rate BH of the protective ring capacitance is greater than the preset change rate threshold b0, then the environmental gain coefficient is updated to {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is the update coefficient and HK is the environmental gain coefficient before the update; otherwise, the environmental gain coefficient is not updated.

7. The method according to claim 1, characterized in that, Based on the fundamental amplitude of the current signal within the monitoring period and the environmental gain coefficient, a current correction coefficient is constructed, including: The current correction weighting factor is determined based on the fundamental amplitude of the current signal within the monitoring period. The current correction coefficient is constructed based on the current correction weight shadow and the environmental gain coefficient.

8. The method according to claim 7, characterized in that, The expression for the current correction weighting factor is: In the formula, W For current correction weighting factor, F 1 represents the fundamental amplitude during the monitoring period; F n is the amplitude of the nth harmonic.

9. The method according to claim 7, characterized in that, The current correction coefficient is constructed based on the current correction weight shadow and the environmental gain coefficient, including: When the current correction weight factor is less than or equal to the compensation threshold r0, the current correction coefficient is constructed as [z1×(1-0.1×W)×environmental gain coefficient], otherwise the current correction coefficient is constructed as [z2×(1-0.1×W)×environmental gain coefficient], where z1 is the first compensation factor and z2 is the second compensation factor.

10. The method according to claim 1, characterized in that, The amplitude of each harmonic of the calibration current is Fnjj = Fnj × current correction coefficient, where Fnj is the measured value of the nth harmonic amplitude in the next monitoring cycle. The harmonic phases of the calibration current njj= nj+θn, nj is the measured value of the nth harmonic phase in the next monitoring cycle; θn is the nth harmonic offset.

11. A remote calibration device for metrology equipment, used to implement the method described in any one of claims 1-10, characterized in that, include: The calculation module is used to calculate the loss index based on the current characteristics of the current signal extracted within the monitoring period, and to determine the phase offset of each harmonic based on the loss index. The first construction module is used to construct the environmental gain coefficient based on the ambient temperature and humidity during the environmental management cycle. The second construction module is used to construct a current correction coefficient based on the fundamental amplitude of the current signal during the monitoring period and the environmental gain coefficient. The calibration module is used to correct the amplitude of each harmonic in the next monitoring cycle according to the current correction coefficient, and to correct the phase of each harmonic in the next monitoring cycle according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

12. A computer-readable storage medium, characterized in that, The storage medium stores a computer program for performing the method described in any one of claims 1-10.

13. An electronic device, characterized in that, The electronic device includes: processor; Memory used to store the processor's executable instructions; The processor is configured to read the executable instructions from the memory and execute the instructions to implement the method described in any one of claims 1-10.

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