Pulsed radiator

Abstract

The application provides a pulse radiator, relates to the field of microwave radio frequency technology, and comprises a radio frequency multistage amplification link and a measurement and control communication component; the radio frequency multistage amplification link generates an output pulse signal; the measurement and control communication component performs real-time monitoring and regulation on the output pulse signal, and is configured with a self-adaptive degradation fault prevention shutdown control strategy. In a continuous radiation working mode, operating state parameters are continuously acquired; when the operating state parameters reach a preset warning limit, the self-adaptive degradation control is triggered, a dynamic attenuation control code is issued to reduce the output gain to enter a degradation working mode; during the degradation working mode, the parameter development trend is continuously monitored; when the parameters recover to a safe interval, the dynamic attenuation control code is reversely adjusted to smoothly recover the output gain to the initial setting state. The application prevents hard power-off shutdown of the equipment caused by abnormal working conditions, and maintains continuous radiation of the signal.

Description

Technical Field

[0001] This invention relates to the field of microwave radio frequency technology, and particularly to pulse radiators. Background Technology

[0002] Pulse radiators typically utilize multi-stage RF amplification links to achieve power conversion and outward radiation of microwave baseband signals. Under long-term continuous high-load operation, the power transistor arrays within the RF multi-stage amplification links generate relatively concentrated heat dissipation. Limited by the physical tolerances of the underlying hardware assembly's thermal resistance, the junction temperature rise rate of multi-channel parallel-operated amplification modules becomes discrete, leading to asymmetrical drift in the input and output impedances of each branch transistor. This impedance drift disrupts the parallel matching state within the microwave power combining module, easily inducing microwave reflection standing wave internal losses within the system, resulting in accelerated local heat accumulation and uneven power supply current.

[0003] To prevent irreversible thermal breakdown damage to the underlying RF hardware, existing equipment control systems typically incorporate power-off protection logic based on fixed parameter limits. When the sensor detects that the internal component temperature or the absolute level of the standing wave reflection exceeds the set safety boundary, the power switch control circuit directly cuts off the DC power supply path to the multi-stage RF amplification link, thereby terminating the RF microwave output oscillation mechanism. This high-voltage power supply cut-off protection action ensures the safe physical operation of core components.

[0004] Directly cutting off the power supply to the entire system will cause the RF equipment to lose its microwave signal transmission capability, resulting in a complete halt to external radiation operations. In complex environments facing occasional local impedance degradation or critical thermal loads, physically cutting off the power reduces the continuity of equipment operation. Some equipment has a closed-loop automatic level control process. When local standing wave losses cause a drop in the total forward radiated power collected by the detector, the feedback control algorithm will issue a compensation command to increase the front-stage RF drive based on the error, pushing up the RF excitation amplitude. This causes the amplification branch in a local mismatch to bear a more severe RF thermal load, thereby accelerating the triggering of the power-off shutdown mechanism. Summary of the Invention

[0005] The purpose of this invention is to provide a pulse radiator to solve the technical problems mentioned in the background art, such as existing devices triggering power-off protection when facing local impedance degradation or critical thermal load conditions, resulting in a complete cessation of microwave radiation, and closed-loop feedback control increasing RF excitation and thus increasing the thermal load of mismatched branches.

[0006] This invention provides a pulse radiator, including a radio frequency multi-stage amplification link and a measurement and control communication component; the radio frequency multi-stage amplification link generates an output pulse signal; the measurement and control communication component is configured to perform real-time monitoring and feedback control of the radio frequency multi-stage amplification link; The measurement and control communication component is configured with an adaptive degradation fault-prevention shutdown control strategy; the execution steps of the adaptive degradation fault-prevention shutdown control strategy include: In continuous radiation mode, the operating status parameters of the radio frequency multi-stage amplification link are continuously acquired; When the operating status parameters reach the preset warning limit, the measurement and control communication component triggers adaptive degradation control, which reduces the output gain of the radio frequency multi-stage amplification link by issuing a dynamic attenuation control code, thus triggering entry into the degradation operation mode. During the degraded operation mode, the development trend of the operation status parameters is continuously monitored; When the operating status parameters return to the safe range, the measurement and control communication component reverses the dynamic attenuation control code, so that the output gain of the RF multi-stage amplification link smoothly returns to the initial setting state.

[0007] Optionally, the RF multi-stage amplification link includes a pre-stage driver component, a secondary driver component, and a final stage combining component; the pre-stage driver component integrates an electrically adjustable attenuator. The attenuation of the electrically adjustable attenuator is controlled by the measurement and control communication component; The final-stage synthesis component includes a microstrip power divider synthesis module and a waveguide power divider synthesis module.

[0008] Optionally, the output terminal of the RF multi-stage amplification link is provided with a forward coupler, a reverse coupler, and a detector; The operating status parameters monitored by the measurement and control communication component include forward detection voltage and reverse detection voltage; The detector includes a forward detection branch and a reverse detection branch; both the forward and reverse detection branches include a broadband envelope detector diode network and a temperature compensation impedance unit; the temperature compensation impedance unit includes a DC bias compensation network composed of a negative temperature coefficient thermistor and a metal film resistor, wherein the negative temperature coefficient thermistor and the broadband envelope detector diode network are closely mounted and share the same copper-plated grounded thermal conductive area.

[0009] Optionally, the measurement and control communication component acquires externally input frequency data, determines the corresponding target detection voltage based on the mapping relationship, and then enters the closed-loop automatic level control process; In the closed-loop automatic level control process, the measurement and control communication component dynamically adjusts the attenuation value of the electrically adjustable attenuator to ensure that the positive detection voltage matches the target detection voltage.

[0010] Optionally, the pulse radiator further includes a power switch control circuit; The measurement and control communication component is connected to the power switch control circuit; When the operating status parameters exceed the limit protection threshold, the measurement and control communication component sends a power-off control signal to the power switch control circuit to block the power supply to the radio frequency multi-stage amplification link.

[0011] Optionally, the RF multi-stage amplification link includes multiple parallel amplification modules; When the power supply current imbalance of the multi-channel parallel amplifier module exceeds the preset alarm threshold, the measurement and control communication component triggers the adaptive degradation control and suspends the execution of the closed-loop automatic level control process.

[0012] Optionally, during the adaptive degradation control process, the measurement and control communication component also acquires the internal module temperature rise rate; when both the internal module temperature rise rate and the reverse detector voltage rise rate exceed the preset rate reference, the measurement and control communication component reconstructs the dynamic attenuation control code and synchronously lowers the duty cycle of the pulse excitation signal of the internal digital pulse modulation generator to reduce microwave peak heat dissipation.

[0013] Optionally, after entering the degraded operation mode, the system is in a low-power safety maintenance state; When in the low-power safety maintenance state, the measurement and control communication component recalculates and maps the degraded target detection voltage based on the real-time ratio of the forward detection voltage to the reverse detection voltage, thereby maintaining the continuous radiation of the radio frequency pulse signal.

[0014] Optionally, the measurement and control communication component is provided with limiting conditions to activate the reverse adjustment and recovery mechanism; the limiting conditions include: the internal module temperature rise rate turns into a negative value and the absolute value remains stable, while the real-time temperature of the internal module obtained by the sensor falls back to below the preset safe temperature limit, and the power supply current imbalance falls back to below the preset warning limit and no longer fluctuates within the preset time window.

[0015] Optionally, during the reverse adjustment of the dynamic attenuation control code, the measurement and control communication component gradually reduces the attenuation of the electrically adjustable attenuator; after each reduction in attenuation, the power supply current imbalance is continuously checked. When the output gain of the RF multi-stage amplification link returns to the initial set state, the measurement and control communication component resumes the closed-loop automatic level control process.

[0016] The present invention has achieved the following beneficial effects: The adaptive degradation and fault-prevention shutdown control strategy configured in this invention can, when the operating status parameters reach a preset warning limit but have not yet reached the ultimate protection limit, actively send dynamic attenuation control codes through the measurement and control communication component to reduce the output gain of the RF multi-stage amplification link, guiding the system to smoothly transition to a low-power safety maintenance state. This underlying intervention control mechanism reduces the peak heat dissipation and internal reflection standing wave loss of the RF power transistor, maintaining the basic microwave pulse signal continuous external radiation while ensuring that the RF amplification components do not suffer thermal breakdown damage, thus avoiding unplanned equipment shutdown caused by directly cutting off the DC power supply. During the degradation operation phase, the measurement and control communication component recalculates the degradation target detection voltage based on the real-time ratio of the forward and reverse detection voltages, preventing secondary overload heating caused by the closed-loop automatic level control process pushing up the RF excitation due to misjudgment of the total system power drop. Once the internal module's absolute temperature and power supply current imbalance are detected to naturally fall back to a safe range and remain stable, the system can gradually reverse the dynamic attenuation control code according to the timing verification process, so that the microwave output gain smoothly returns to the initial setting state, improving the equipment's operational continuity and adaptive adjustment capability under dynamic thermal environments and complex loads.

[0017] Other features and advantages of the invention will be set forth in the following description, and will be apparent in part from the description, or may be learned by practicing the invention. The objects and other advantages of the invention may be realized and obtained by means of the structures particularly pointed out in the written description and the accompanying drawings.

[0018] The technical solution of the present invention will be further described in detail below with reference to the accompanying drawings and embodiments. Attached Figure Description

[0019] The accompanying drawings are provided to further illustrate the invention and form part of the specification. They are used in conjunction with embodiments of the invention to explain the invention and do not constitute a limitation thereof. In the drawings: Figure 1 This is a schematic diagram of the overall system structure and control signal link of the pulse radiator in an embodiment of the present invention; Figure 2 This is a diagram showing the physical connection hierarchy of the internal components of the radio frequency multi-stage amplification link in an embodiment of the present invention. Figure 3 This is a block diagram showing the internal structure of the bidirectional branch of the detector and its connection with the measurement and control communication component in an embodiment of the present invention. Figure 4 This is the main flowchart of the adaptive degradation and fault-prevention shutdown control strategy in this embodiment of the invention; Figure 5 This is a detailed logic flowchart of triggering adaptive degradation control and reconstructing target parameters in an embodiment of the present invention; Figure 6This is a flowchart illustrating the execution of the reverse adjustment and recovery mechanism after the specified conditions are met in this embodiment of the invention. Detailed Implementation

[0020] The preferred embodiments of the present invention will be described below with reference to the accompanying drawings. It should be understood that the preferred embodiments described herein are for illustration and explanation only and are not intended to limit the present invention.

[0021] like Figure 1 As shown, the pulse radiator includes a multi-stage radio frequency (RF) amplification link and a measurement and control communication component. The RF multi-stage amplification link is configured to receive externally modulated microwave baseband signals and utilize internally cascaded solid-state semiconductor transistors to perform RF power conversion and amplification processes, generating an output pulse signal. The measurement and control communication component is configured to perform real-time monitoring and feedback control of the RF multi-stage amplification link. The measurement and control communication component internally includes a microprocessor chip, a multi-channel analog-to-digital converter chip, a digital-to-analog converter chip, and a non-volatile memory chip. The measurement and control communication component connects to each monitoring node of the RF multi-stage amplification link via a control bus and a data bus, collects underlying physical operating parameters, and outputs a sequence of digital control commands based on logical judgment results.

[0022] It should be specifically noted that, unless otherwise explicitly stated otherwise, all microprocessor chips, sensor components, basic radio frequency microwave devices (such as electrically adjustable attenuators, couplers, detector diodes, etc.) and related basic circuit units involved in the embodiments of this invention are existing technologies or commercially available known products in the field. Those skilled in the art, knowing the overall system topology and control logic disclosed in this application, can implement the hardware functions of the above components using conventional technical means, combined with common knowledge in the field and conventional technical manuals, without requiring any creative effort. Since the specific internal circuit structure and microscopic physical principles of the above-mentioned basic components are not the substantial improvements of this invention, to avoid redundancy in the specification and to highlight the core inventive points of this invention, the specific internal structures of such prior art will not be described in detail here.

[0023] like Figure 2 As shown, in the physical connection sequence of the RF multi-stage amplification link, the RF multi-stage amplification link includes a pre-stage driver component, a secondary driver component, and a final-stage synthesizer component connected in series along the microwave energy transmission path. The pre-stage driver component is located at the first physical input position of the RF multi-stage amplification link, receiving the initial microwave excitation RF waveform generated by the frequency generator. The pre-stage driver component internally has a pre-amplification network that performs primary RF gain boosting on the initial microwave excitation RF waveform. The pre-amplification network includes RF impedance matching traces and a low-noise amplifier die.

[0024] Furthermore, the pre-stage driver assembly integrates an electrically adjustable attenuator. The electrically adjustable attenuator is physically connected in series with the main RF microwave transmission line of the pre-stage driver assembly. The attenuation of the electrically adjustable attenuator is controlled by the measurement and control communication assembly.

[0025] Specifically, the electrically adjustable attenuator adopts a digitally stepped variable attenuation topology composed of multi-stage digitally controlled RF switches and a passive attenuation resistor network. The electrically adjustable attenuator has a multi-bit digital parallel control interface. The measurement and control communication component sends binary-width dynamic attenuation control codes to the multi-bit digital parallel control interface via the control bus. Different combinations of dynamic attenuation control codes control the on / off states of the multi-stage digitally controlled RF switches inside the electrically adjustable attenuator, causing the RF microwave signal passing through the electrically adjustable attenuator to flow through a specific combination of passive attenuation resistor networks, thereby adjusting the insertion loss value on the main RF microwave transmission line. The measurement and control communication component sets the RF excitation amplitude entering the subsequent cascaded amplification module by adjusting the insertion loss value.

[0026] After being amplified and amplitude-conditioned by the pre-stage driver component, the radio frequency (RF) microwave signal is fed into the RF input terminal of the secondary driver component via a microwave RF coaxial cable. The secondary driver component employs gallium nitride (GaN) power transistors to construct an active microwave amplifier circuit. The secondary driver component performs power amplification on the received microwave signal, ensuring that the output RF level meets the input drive power requirements of the subsequent transistor array. The secondary driver component internally includes an independent bias voltage supply network for stabilizing the static operating node of the GaN power transistors.

[0027] The RF output port of the secondary drive component is connected to the RF input port of the final-stage combining component via a microstrip connection transmission line. The final-stage combining component includes a microstrip power divider combining module and a waveguide power divider combining module. The microstrip power divider combining module uses a microwave dielectric copper-clad laminate as the RF circuit printed circuit substrate. The RF input terminal of the microstrip power divider combining module receives the RF waveform output from the secondary drive component and, using a multi-stage microstrip power divider network, divides the RF waveform into equal-amplitude and in-phase segments, evenly distributing them to multiple parallel-connected final-stage power amplifier sub-branch lines.

[0028] The radio frequency multi-stage amplification link includes multiple parallel amplification modules. These modules are distributed and soldered onto multiple parallel final-stage power amplification sub-branch lines. Each parallel amplification module includes a high-power gallium nitride (GaN) power field-effect transistor. Each parallel amplification module receives the distributed branch radio frequency drive signals and outputs amplified branch microwave pulses using DC power supplied by a DC distribution network. These amplified branch microwave pulses are then combined through a symmetrical microstrip combining network in the downstream topology of the microstrip power divider / combiner module.

[0029] The microstrip power divider / combiner module has a microstrip-to-waveguide transition structure at its output. The aggregated microwave signal is injected into the waveguide power divider / combiner module via this transition structure. The waveguide power divider / combiner module is composed of a metal-enclosed rectangular waveguide cavity assembly. The multi-branched microwave energy is vector-superimposed and combined within the metal-enclosed rectangular waveguide cavity of the waveguide power divider / combiner module through a spatial transverse electric mode electromagnetic field, ultimately forming a concentrated output pulse signal at the waveguide output interface.

[0030] To extract the actual radiated power of the output pulse signal and the load-end matching impedance feedback parameters, the output end of the RF multi-stage amplification link is equipped with a forward coupler, a reverse coupler, and a detector. The forward coupler and the reverse coupler are sequentially connected in series on the microwave output main transmission channel at the end of the waveguide power divider and combiner module. The forward coupler extracts the proportionally attenuated forward microwave sampling RF signal along the direction of electromagnetic wave propagation based on the directional coupling window. The coupling window of the reverse coupler is arranged in the opposite direction to that of the forward coupler, and is used to extract the reverse microwave sampling RF signal that is folded back into the metal-enclosed rectangular waveguide cavity when there is a microwave impedance mismatch at the antenna end or the transmission feeder end.

[0031] The detector is connected to the RF output ports of both the forward and reverse couplers. For example... Figure 3 As shown, the detector includes a forward detection branch and a reverse detection branch. Both the forward and reverse detection branches include a broadband envelope detector diode network, a temperature-compensated impedance unit, and a smoothing low-pass filter circuit.

[0032] Specifically, microwave broadband envelope detector diodes exhibit intrinsic temperature drift (typically 100°C) due to the nonlinear drop in forward voltage drop as the physical junction temperature increases. Unlike simple software numerical correction, the temperature compensation impedance unit employs a hardware DC bias compensation network composed of a negative temperature coefficient (NTC) thermistor and a metal film resistor. On the printed circuit board (PCB) physical layout, this NTC thermistor is closely mounted to the detector diode and shares the same copper-clad grounded thermal conductive area, ensuring consistent thermal coupling at the bottom layer. When the RF cavity heat dissipation causes a negative drop in the diode detection level, the resistance of the NTC thermistor in the same temperature range decreases synchronously, dynamically reducing the voltage division insertion loss of the DC bias network. By utilizing the physical potential rise of the passive network, the voltage drop of the diode's pre-voltage drop is proportionally and promptly offset, improving the reference stability of the RF envelope conversion level over a wide temperature range from a hardware perspective.

[0033] A broadband envelope detector diode network strips the high-frequency microwave carrier envelopes of both the forward and reverse microwave sampling RF signals, converting them into analog level signals. A smoothing low-pass filter circuit absorbs and filters out RF ripple components, outputting a continuous DC analog parameter. After processing by the detector, the forward microwave sampling RF signal is converted into a forward detector voltage, and the reverse microwave sampling RF signal is converted into a reverse detector voltage.

[0034] The operating status parameters monitored by the measurement and control communication component include the forward detection voltage and the reverse detection voltage. The forward detection voltage represents the actual forward output power level radiated into external space by the RF multi-stage amplification link at the current moment; the reverse detection voltage represents the external microwave standing wave reflection parameters faced by the pulse radiator at the current moment. The multi-channel analog-to-digital converter chip in the measurement and control communication component performs analog-to-digital conversion on the forward and reverse detection voltages according to the discrete sampling clock cycle, extracting the corresponding digital value sequences and storing them in the storage buffer. The microprocessor chip extracts the digital value sequences and performs digital smoothing filtering operations to filter out voltage surge pulses.

[0035] Specifically, considering the pulse envelope characteristics of the radio frequency microwave signal during detection and the transient white noise caused by spatial electromagnetic coupling, the digital smoothing filtering operation does not employ the common continuous-time low-pass filtering algorithm, but instead uses a synchronous sliding extreme value averaging algorithm that closely matches the microwave physical timing. Its execution steps and constraints are as follows: the microprocessor chip, based on the internally set current pulse repetition frequency (PRF), calculates the length of the sliding data window... Locked to (in (This refers to the fixed sampling frequency of the analog-to-digital converter chip). The physical purpose of this hardware timing binding is to ensure that a single computation window accurately and completely spans a microwave physical transceiver cycle. Within a single window, the highest and lowest 5% extreme values ​​are removed (physically corresponding to removing nanosecond-level high-amplitude spikes induced by spatial electromagnetic arcing), and then the arithmetic mean of the remaining samples is calculated. This design decouples the actual RF power envelope from the high-frequency noise floor at the underlying level, avoiding distortion of the effective edge of the pulse envelope caused by excessive smoothing in conventional software filtering.

[0036] During the conventional continuous radiation operation mode, since the internal gain index of the microwave power transistor will drift nonlinearly with the device temperature, the measurement and control communication component acquires the external input frequency data, determines the corresponding target detection voltage based on the mapping relationship, and then enters the closed-loop automatic level control process.

[0037] Before entering the closed-loop automatic level control process, the measurement and control communication component acquires the transmission frequency data and the set value of the RF pulse target output power. The non-volatile memory chip inside the measurement and control communication component stores a full-band calibration nonlinear mapping data matrix table. This full-band calibration nonlinear mapping data matrix table records the digital target detection voltage reference bound to the corresponding output power achieved by the pulse radiator at each discrete frequency point across the full band. After reading the frequency data, the measurement and control communication component performs search and interpolation operations in the full-band calibration nonlinear mapping data matrix table to extract the target detection voltage corresponding to the current operating frequency point and the set value of the RF pulse target output power.

[0038] In the closed-loop automatic level control process, the measurement and control communication component periodically extracts the converted real-time positive detection voltage sample and performs a difference subtraction operation between the positive detection voltage sample and the extracted target detection voltage. Based on the calculated positive and negative error values, the microprocessor chip calculates the control digital offset using a proportional-integral adjustment algorithm.

[0039] Specifically, in the extraction logic of the full-band calibration nonlinear mapping data matrix table, the search and interpolation operations specifically adopt the bilinear interpolation algorithm, which searches for the four nearest factory physical calibration points in the three-dimensional mapping data based on the real-time frequency and target power to perform spatial weight interpolation.

[0040] The proportional-integral control algorithm employs a discrete-time positional formula suitable for microcontrollers: .in, For the first The control digital offset is calculated from each sampling period; The positive or negative error value is obtained by subtracting the difference between the currently sampled positive detector voltage sample and the target detection voltage; This is the discrete cumulative sum of errors from the start of the closed loop to the current time. It is the proportional gain constant. is the integral gain constant. and The value is based on the physical delay time (nanosecond to microsecond) established by the RF envelope of the pre-stage driver component and the final stage synthesizer component under factory conditions. It is obtained by pre-tuning in the open-loop step test of the device using the Ziegler-Nichols critical scaling method. Its purpose is to block the high-frequency oscillation that is easy to be generated when the microwave power approaches the target amplitude from the bottom layer.

[0041] The measurement and control communication component adds the control digital offset to the current attenuation status word to generate a new round of dynamic attenuation control code. The measurement and control communication component then sends the dynamic attenuation control code to the electrically adjustable attenuator. If the forward detection voltage is lower than the target detection voltage, the sent dynamic attenuation control code instructs the electrically adjustable attenuator to reduce the insertion loss amplitude of the physical transmission link and increase the RF excitation amplitude envelope level fed into the secondary drive component; if the forward detection voltage is higher than the target detection voltage, the sent dynamic attenuation control code instructs the electrically adjustable attenuator to increase the insertion loss amplitude and decrease the RF excitation amplitude envelope level. The measurement and control communication component dynamically adjusts the attenuation value of the electrically adjustable attenuator to ensure that the forward detection voltage matches the target detection voltage and maintains a constant output pulse envelope amplitude.

[0042] The pulse radiator also includes a power switch control circuit. The measurement and control communication component is electrically connected to the power switch control circuit. The power switch control circuit is connected in series between the DC power supply module and the drain DC power distribution busbars of each power amplifier transistor in the RF multi-stage amplification link. The power switch control circuit is composed of a parallel array of solid-state metal-oxide-semiconductor field-effect transistors and is equipped with a charge and discharge drive channel. The measurement and control communication component defines limit protection limits for operating status parameters. The limit protection limits include the maximum operating physical temperature limit, the maximum reverse standing wave absolute voltage threshold, and the maximum safe total current threshold.

[0043] The measurement and control communication component continuously extracts multi-channel sensor data sequences during the monitoring process. When the captured operating status parameters exceed the limit protection threshold, the microprocessor chip interrupts the regular calculation thread. The measurement and control communication component sends a low-level power-off control signal to the power switch control circuit. Upon receiving the power-off control signal, the power switch control circuit performs a charge extraction action to disconnect the conduction channel of the internal solid-state field-effect transistor array. The cut-off action physically disconnects the high-voltage DC power supply path, blocks the power supply to the RF multi-stage amplification link, and terminates the RF microwave output oscillation mechanism to prevent hardware thermal damage.

[0044] Triggering the aforementioned limit protection boundary, resulting in a physical power cutoff to the hardware, will cause the device to stop working. To maintain stable operation of the system when facing local impedance degradation or thermal accumulation, the measurement and control communication component is configured with an adaptive degradation fault-prevention shutdown control strategy. The overall process of the adaptive degradation fault-prevention shutdown control strategy is as follows: Figure 4 As shown, it includes the following execution steps.

[0045] Step S1: In continuous radiation mode, continuously acquire the operating status parameters of the radio frequency multi-stage amplification link.

[0046] Operating parameters include forward detection voltage, reverse detection voltage, internal module temperature rise rate, reverse detection voltage rise rate, and power supply current imbalance. The RF multi-stage amplification link includes multiple parallel amplification modules. Under stable RF load matching conditions, the RF microwave energy injected into each of the multiple parallel amplification modules is equal, and the DC current consumed by each branch tends to be consistent. When prolonged high-load operation or external load microwave standing wave reflection occurs, the thermal resistance at the bottom of the multiple parallel amplification modules has tolerances, resulting in discrete rates of transistor junction temperature accumulation. The difference in junction temperature rise causes asymmetric drift in the transistor input and output impedances. This asymmetric drift in RF microwave impedance disrupts the parallel matching network state within the microstrip power divider and combiner module, inducing microwave reflection standing wave internal losses between the parallel network ports. The reflection standing wave internal losses manifest as discrete changes in the DC current values ​​of each branch.

[0047] The measurement and control communication component has shunt current sensing resistors connected in series on the power supply branches from the DC distribution bus to each multi-channel parallel amplifier module. The component triggers a multi-channel analog-to-digital converter chip according to a fixed clock, polling and sampling the voltage drop signal across each shunt current sensing resistor to extract the real-time absolute current value queue for each parallel amplifier branch. The microprocessor chip extracts the peak current scalar and valley current scalar from the real-time absolute current value queue, accumulates the current values ​​of all branches, and calculates the average expected value parameter. The microprocessor chip calculates the absolute value of the difference between the peak current scalar and the valley current scalar, divides the absolute value of the difference by the average expected value parameter, and calculates the power supply current imbalance.

[0048] Temperature sensors distributed across each multi-channel parallel amplification module upload temperature values ​​in real time. The measurement and control communication component maintains a sliding-time data queue in its storage area, storing high-frequency sampled temperature value sequences and reverse detection voltage value sequences within a preset sampling time period. The component extracts the temperature difference between the beginning and end of the sliding-time data queue and divides it by the corresponding time span value to calculate the internal module's temperature rise rate. The component performs the same differential operation on the reverse detection voltage value sequence to calculate the reverse detection voltage rise rate.

[0049] Step S2: When the operating status parameter reaches the preset warning limit, the measurement and control communication component triggers adaptive degradation control, which reduces the output gain of the RF multi-stage amplification link by sending a dynamic attenuation control code, triggering entry into the degradation operation mode.

[0050] The preset warning limits include a preset alarm threshold for power supply current imbalance, a preset rate reference for internal module temperature rise rate, and a preset rate reference for reverse detector voltage rise rate. The numerical parameters corresponding to these preset warning limits are all lower than the aforementioned limit protection limits.

[0051] More precisely, the specific value ranges and physical derivation methods of each limit and threshold parameter are as follows: The maximum safe total current threshold in the limit protection limit is set to 80% to 90% of the sum of the continuous drain current limits specified in the factory datasheet of each gallium nitride transistor in the multi-channel parallel amplification module; the preset alarm threshold value range of the power supply current imbalance is set to 10% to 15%, determined by the maximum off-center load tolerance percentage of each microstrip power divider and combining module branch under the limit thermal tolerance without causing the non-inductive thin-film isolation resistor to burn out; the preset rate reference calibration of the internal module temperature rise rate is 1.5℃ / s to 2.5℃ / s, derived by dividing the maximum tolerable heat dissipation power allowed by the RF amplification link by the physical thermal constant of the bottom metal substrate and heat sink; the preset rate reference of the reverse detector voltage rise rate is set to 5% / s to 10% / s of the full-scale detector voltage, and the boundary constraint is based on the measured envelope slope when the microwave standing wave change is induced by high-speed arcing or physical icing at the antenna end.

[0052] When the power supply current imbalance of the multi-channel parallel amplifier module exceeds the preset alarm threshold, it indicates that a local parallel amplification branch transistor in the microstrip power divider and combiner module region is at the thermal distribution boundary. If the system continues to execute the closed-loop automatic level control process at this time, the system control algorithm will output a gain increase compensation code due to the decrease in total power acquired by the forward detector voltage, pushing up the RF excitation amplitude, causing the locally mismatched amplification branch to bear a more severe RF thermal load.

[0053] Combination Figure 5 As shown in the detailed degradation control logic flow diagram, when the power supply current imbalance exceeds the preset alarm threshold, the measurement and control communication component triggers the adaptive degradation control and suspends the execution of the closed-loop automatic level control process. After suspending the closed-loop automatic level control process, the measurement and control communication component cuts off the feedback compensation calculation logic for the external closed-loop gain boost. The input RF drive microwave excitation level of the system's front-end stops automatic rise compensation calculation, and the character code is locked within the current control state character code parameters.

[0054] During the adaptive degradation control process, the measurement and control communication component also acquires the internal module temperature rise rate. When both the internal module temperature rise rate and the reverse detector voltage rise rate exceed a preset rate reference, the measurement and control communication component reconstructs the dynamic attenuation control code and simultaneously reduces the duty cycle of the pulse excitation signal of the internal digital pulse modulation generator to reduce microwave peak heat dissipation. Specifically, the measurement and control communication component extracts the corresponding attenuation compensation constant from the storage matrix table based on the magnitude by which the internal module temperature rise rate and the reverse detector voltage rise rate exceed the preset rate reference.

[0055] The storage area matrix is ​​a two-dimensional discrete lookup table structure embedded in a non-volatile memory chip. The specific extraction and mapping steps are as follows: the microprocessor chip calculates the first difference between the current internal module temperature rise rate and its preset rate reference, and the second difference between the reverse detector voltage rise rate and its preset rate reference; the first and second differences are divided by a preset quantization resolution step size and rounded down to directly obtain the corresponding row and column index numbers; the microprocessor chip performs cross-addressing based on the row and column index numbers to retrieve the binary digital code stored in the address node as the attenuation compensation constant. This constant is physically equivalent to the physical insertion loss bit width step (LSB) of the multi-stage digitally controlled RF switches inside the electrically tunable attenuator, with values ​​arranged in a positively correlated stepwise manner to ensure that the degradation process matches the discrete control accuracy of the hardware attenuator.

[0056] The telemetry and communication component adds the attenuation compensation constant to the current dynamic attenuation control code, generates a reconstructed dynamic attenuation control code, and sends it to the electrically adjustable attenuator. The electrically adjustable attenuator responds to the digital command by increasing the insertion loss resistance of the RF line, thus reducing the RF excitation envelope amplitude entering the secondary drive component and the final synthesis component. Simultaneously, the telemetry and communication component modifies the pulse control register parameters of the internal digital pulse modulation generator, reducing the duration of the high-level pulse transmission while maintaining the pulse repetition frequency. By reducing the amplitude envelope of the microwave signal and the proportion of RF energy radiation time through the reconstructed dynamic attenuation control code, the overall microwave peak heat dissipation of the system is reduced. The system then enters a degraded operation mode.

[0057] Step S3: During the degraded operation mode, continuously monitor the development trend of the operation status parameters.

[0058] After entering the degraded operation mode, the system is in a low-power safety maintenance state. In this state, the total output gain of the RF multi-stage amplification link is suppressed. The target detection voltage parameters used in the original closed-loop automatic level control process, which correspond to the high-power full-load operating state, are no longer applicable to the degraded microwave operating parameters. In this low-power safety maintenance state, the measurement and control communication component recalculates and maps the degraded target detection voltage based on the real-time ratio of the forward detection voltage to the reverse detection voltage, thereby maintaining continuous RF pulse signal radiation.

[0059] The process for recalculating and mapping the degraded target detection voltage is as follows: Within the analog-to-digital sampling period after the issuance of the reconstructed dynamic attenuation control code and the duty cycle parameter adjustment command, the measurement and control communication component extracts the degraded real-time forward detection voltage value and the real-time reverse detection voltage value. The microprocessor chip divides the real-time reverse detection voltage value by the real-time forward detection voltage value to obtain the real-time reflection ratio coefficient reflecting the load standing wave matching degree. The measurement and control communication component extracts the nominal open-loop forward detection voltage reference value corresponding to the currently reconstructed dynamic attenuation control code from the degraded power mapping data table defined in its internal storage area. The microprocessor chip multiplies the nominal open-loop forward detection voltage reference value by a correction function including the real-time reflection ratio coefficient to calculate the degraded target detection voltage.

[0060] The specific mathematical expression for the correction function is defined as follows: .in, To calculate the amount of the generated correction function; The real-time reflection scaling factor (i.e., the quotient of the real-time reverse detection voltage value divided by the real-time forward detection voltage value) is given by the given value. ); The system's microwave internal loss compensation reduction factor ranges from 0.6 to 0.85, and is calibrated based on the standing wave heat dissipation conversion rate of the isolation resistor within the microstrip power divider module. The physical derivation of this formula is based on the microwave transmission line principle: the net transmitted microwave power effectively radiated into space by the RF link is equivalent to the forward incident power minus the reflected standing wave power; that is, the net radiation ratio is proportional to... By multiplying the target detection voltage by this correction function, the closed-loop algorithm avoids improper compensation logic from the underlying principle of electromagnetic wave energy conservation (i.e., avoids the system from excessively issuing instructions to increase the RF gain due to the detector's misjudgment of a decrease in the total power radiated outwards). This effectively prevents secondary thermal breakdown of the RF transistor caused by compensation overload, and its execution efficiency is superior to conventional algorithms.

[0061] The telemetry and communication component overwrites the degraded target detection voltage into the current feedback closed-loop comparison register. The telemetry and communication component activates the closed-loop adjustment calculation process under constrained low-power conditions, performing a difference comparison operation between the subsequently acquired forward detection voltage and the degraded target detection voltage. Based on the error, the telemetry and communication component executes closed-loop increase / decrease adjustment commands based on the reconstructed dynamic attenuation control code. This adjustment process ensures that the RF multi-stage amplification link maintains a stable amplitude microwave signal radiation under low-power safety maintenance conditions.

[0062] During the system's low-power safety maintenance state, overall heat dissipation decreases, and external physical heat dissipation equipment continues to operate. The measurement and control communication component is equipped with limiting conditions to activate the reverse adjustment recovery mechanism. The limiting conditions include: the internal module temperature rise rate becomes negative and the absolute value remains stable; simultaneously, the real-time temperature of the internal module acquired by the sensor falls below the preset safe temperature limit; and the power supply current imbalance falls below the preset warning limit and no longer fluctuates within a preset time window.

[0063] The specific logical process for determining whether the aforementioned limiting conditions are met is as follows: The measurement and control communication component performs differential calculations on the temperature sensor data collected over a continuous time series. When the result of the differential calculation enters the negative domain, it indicates that the internal heating rate is lower than the outward heat transfer rate, and the internal module temperature rise rate becomes negative. The measurement and control communication component extracts a sample array of negative internal module temperature rise rates from multiple consecutive periods and calculates the mathematical variance of the sample array. When the mathematical variance parameter is lower than a set variance threshold constant, it indicates that the temperature decrease process has converged, confirming that the absolute value of the temperature rise rate remains stable. The exact value of the variance threshold constant is defined as between 0.02 and 0.06. The constant is calculated by combining the inherent background thermal noise amplitude of the system's temperature sensor sampling circuit under the condition of constant temperature in cold equipment and operation of air-cooled fan with the least significant bit (LSB) quantization fluctuation error of the analog-to-digital conversion channel. It is intended to serve as a noise floor boundary to effectively filter out minor fluctuations caused by local physical airflow disturbances in the cavity.

[0064] Simultaneously, the measurement and control communication component determines that the absolute temperature of the internal modules continues to decline and falls below the set safe temperature limit. As the temperature decreases, the microwave impedance drift of each parallel amplification module shrinks. The internal standing wave loss of the microstrip power divider / combiner module decreases. The measurement and control communication component calculates the power supply current imbalance in real time and compares it with a preset warning limit. When the power supply current imbalance falls below the preset warning limit, it indicates that the RF energy transmission state within the RF multi-stage amplification link has returned to physical equilibrium.

[0065] To verify the stability of the state recovery parameters, the measurement and control communication component is configured with a timing verification process. When the measurement and control communication component confirms that the internal module temperature rise rate turns negative and the absolute value remains stable, and that the internal module absolute temperature and power supply current imbalance both meet the condition of being below the preset warning limit, the built-in hardware timer of the measurement and control communication component begins to accumulate clock pulse parameters. During the parameter accumulation process, if the monitored operating status parameter shows a value jump that deviates from the set limit, the current accumulated value of the hardware timer is cleared to zero. Only when all parameter monitoring channels maintain compliant output within the continuous period of the preset time window, and the hardware timer completes uninterrupted accumulation counting, is the measurement and control communication component confirmed that the aforementioned limiting conditions are fully met. The specific duration of the preset time window is set according to the principle that it is greater than or equal to three times the overall physical thermal capacity time constant of the metal base with the largest mass in the RF multi-stage amplification link system (typically configured as 8 to 15 seconds). The physics behind this design is to ensure that the physical cooling process of internal components has fully passed the hysteresis period of transient heat conduction and entered a true thermodynamic convergence steady state, preventing the verification logic from making misjudgments due to the transient cooling of the surface caused by a sharp drop in power.

[0066] Step S4: When the operating status parameters are restored to the safe range, the measurement and control communication component reverses the dynamic attenuation control code to smoothly restore the output gain of the RF multi-stage amplification link to the initial setting state.

[0067] Combination Figure 6 As shown in the reverse adjustment misalignment timing execution logic, after the limiting conditions are met, the measurement and control communication component initiates the reverse adjustment recovery mechanism. During the reverse adjustment of the dynamic attenuation control code, the measurement and control communication component progressively reduces the attenuation of the electrically adjustable attenuator. Specifically, the measurement and control communication component extracts the attenuation reduction step size constant from its internal storage space. The measurement and control communication component subtracts the attenuation reduction step size constant from the reconstructed dynamic attenuation control code to calculate the transitional attenuation control code for the next stage. The measurement and control communication component sends the transitional attenuation control code to the electrically adjustable attenuator, which controls the internal passive network to change the impedance path, reducing the RF physical insertion loss. The RF excitation amplitude then increases step-by-step.

[0068] After each reduction in attenuation, the telemetry and communication component starts a waiting delay instruction program to provide the physical timing period for microwave impedance redistribution.

[0069] The delay period in the state wait delay instruction program is subject to underlying hardware circuit boundary constraints: its specific delay time The configuration is greater than 5 times the physical charge-discharge time constant formed by the resistors and capacitors in the internal smoothing low-pass filter circuit of the detector (i.e., ).in, The specific delay time in the state wait delay instruction program; The resistor is located in the smoothing low-pass filter circuit inside the detector. This refers to the energy storage capacitor in the smoothing low-pass filter circuit inside the detector. The electrical derivation for this setting is based on the following: when the physical attenuation of the electrically adjustable attenuator decreases and the RF drive envelope experiences a step increase, the low-pass filter energy storage capacitor inside the detector needs to re-accumulate charge through an external hardware network. According to the transient characteristics of semiconductors, the voltage response curve of the analog-to-digital conversion node can only reach more than 99.3% of the new steady-state step target after 5 RC time constants. Without this electrical waiting period, the subsequent analog-to-digital conversion channel is highly susceptible to acquiring false, distorted low voltages during the transient ramp-up process, inducing oscillations and misjudgments in the closed-loop algorithm.

[0070] After the delay command cycle ends, the measurement and control communication component collects the parallel branch shunt voltage data again to continuously verify the power supply current imbalance. The measurement and control communication component compares the verified power supply current imbalance with the recovery status verification alarm threshold parameter.

[0071] Specifically, the parameter is a hysteresis limit established according to hardware hysteresis logic. Its specific mathematical relationship is: Recovery state verification alarm threshold parameter = Preset alarm threshold ,in The physical hysteresis band constant is preferably between 0.15 and 0.20. The underlying hardware consideration for introducing this hysteresis band constant is that high-power gallium nitride field-effect transistors exhibit significant semiconductor thermal memory effects and thermal conduction delays in the underlying metal substrate. When the current imbalance just drops to the preset alarm threshold, the transistor junction temperature often has not yet fully dissipated to the safe baseline; if the same threshold is used for judgment and the RF drive is immediately increased, the residual junction temperature will be instantly activated, causing the device to experience high-frequency destructive oscillations (ping-pong effect) between degraded and full-load states. This difference calculation logic provides the necessary cooling and impedance reconstruction physical buffer for the microwave power combining network.

[0072] If the power supply current imbalance is lower than the recovery state verification alarm threshold parameter, the measurement and control communication component continues to perform the subsequent step-by-step transitional attenuation control code subtraction operation and issues commands. If the power supply current imbalance exceeds the recovery state verification alarm threshold parameter during the verification process, the measurement and control communication component suspends the attenuation subtraction action, locks the control code at the current transitional attenuation control code status bit, and waits for the system physical parameters to return to the parameter requirements before re-verifying. On the execution axis of the attenuation decreasing step by step, the measurement and control communication component calls back the pulse excitation signal duty cycle control register data in stages, increasing the high-level time width of a single pulse. The recovery action of the pulse excitation signal duty cycle parameter and the decrement action of the dynamic attenuation control code are set to be staggered in the execution scheduling process to prevent the step of microwave pulse amplitude and the step of pulse width from overlapping in the same control clock command cycle.

[0073] The specific timing isolation rule for the misalignment trigger execution is as follows: After the microprocessor chip sends a decreasing transitional attenuation control code to the electrically tunable attenuator, it immediately starts a hardware anti-collision dead-time delay timer. Only after the timer overflows and is interrupted can the duty cycle width extension instruction be written to the modulation generator. The exact duration of this hardware anti-collision dead-time delay is required to be greater than the physical level switching setup time of the multi-stage digitally controlled RF switches inside the electrically tunable attenuator, plus the sum of the group delay of the gallium nitride transistor in the RF cascade link after receiving the step RF excitation and rebuilding the stable microwave impedance matching field (typical time window dead time value is...). to This time-slot isolation, based on the underlying characteristics of microwave distributed parameters, effectively avoids the rapid multiplication and superposition of energy caused by sudden changes in RF power amplitude and high-level pulse width broadening in a very short time, preventing secondary thermal damage to high-power microwave tubes due to transient surge currents.

[0074] When the value of the transient attenuation control code issued falls back to the initial dynamic attenuation control code constant saved before triggering degradation control, and the duty cycle configuration value of the pulse excitation signal recovers to the initial system setting parameters, the output gain of the RF multi-stage amplification link recovers to the initial setting state. The microwave signal electromagnetic field output of the pulse radiator reaches the set operating physical range.

[0075] When the output gain of the RF multi-stage amplification link returns to the initial set state, the telemetry and communication component resumes the closed-loop automatic level control process. The telemetry and communication component executes a memory clearing command, clearing the data storage address for the degraded target detection voltage used for low-power safety maintenance. The telemetry and communication component retrieves the absolute scalar value of the reference target detection voltage, matching the initially set transmit target power, from the full-band calibration nonlinear mapping data matrix. Simultaneously, the telemetry and communication component rewrites the accumulated cache constant area of ​​the proportional-integral algorithm function with the current initial dynamic attenuation control code value. The multi-channel analog-to-digital converter extracts the sampled value of the forward detector voltage under the reference microwave output, and the telemetry and communication component performs closed-loop subtraction comparison and control offset generation based on the absolute scalar value of the reference target detection voltage. The feedback adjustment power of the RF multi-stage amplification link is transferred back to the reference closed-loop feedback process, and the pulse radiator ends its adaptive degraded state and returns to the normal full-load physical operating mode.

[0076] In the connection structure of the microstrip power divider combining module, non-inductive thin-film isolation resistor units are connected between the RF branch nodes of the microstrip power divider. Under impedance matching operation, the microwave electric field at the physical node of the branch has equipotential characteristics, and no RF current flows through the non-inductive thin-film isolation resistor unit. When external RF load mismatch occurs, and reflected standing waves flow back to the combining node of the microstrip power divider combining module, phasor differences arise in the microwave electric field of each branch. An RF voltage drop is generated across the connected non-inductive thin-film isolation resistor unit, converting RF differential-mode energy into heat energy. During the time period when the measurement and control communication components complete parameter acquisition, calculation, and control command issuance, the isolation resistor unit absorbs transient standing wave energy, providing microwave hardware buffer protection.

[0077] The measurement and control communication component has data validity verification logic configured in its underlying driver program for extracting data sequences. The component reads the detection level parameters of each temperature and current sensor node to verify the connection status of the sensor's peripheral hardware. If a specific sensor channel output terminal exhibits a short-circuit to ground or open-circuit power supply failure characteristic level, it is determined that the short-circuit to ground or open-circuit power supply failure characteristic level has a clear underlying analog-to-digital converter (ADC) digital tolerance range, distinct from theoretical zero-point or full-scale bias logic. This is based on the system's reference voltage. Scale: When the absolute level readings are all within a certain range for more than 10 consecutive hardware sampling cycles. In the low noise range, a short-circuit failure to ground is identified (a 3% margin is reserved to accommodate the thermistor's small voltage drop at extremely low temperatures); when continuous readings are all in the range... In high-voltage areas, the fault is identified as an open circuit or a cold solder joint. This 3% upper and lower limit analog-to-digital guard band design effectively filters out transient overflows in single ADC sampling caused by RF arcing at the high-power antenna end or strong electromagnetic pulse coupling in space, preventing system-level failures caused by the accidental removal of normal sensor nodes. The microprocessor chip removes the sensor data source corresponding to the failed node from the matrix input configuration table. The microprocessor chip extracts monitoring data returned by adjacent healthy sensor nodes and generates alternative estimates using a spatial topological distance inverse weighted average logic to fill in the parameter gaps of the damaged sensor node. The specific generation steps and principles are as follows: Since the multi-channel parallel amplifier module possesses physical spatial wiring symmetry and microwave power equalization characteristics in the RF microstrip power divider network, the measurement and control communication component retrieves the physical coordinate mapping table pre-stored in the memory chip, directly calculates and addresses the two healthy sensor nodes that are closest to the damaged sensor node in terms of straight-line physical distance on the printed circuit board plane; extracts the absolute scalar level of the two healthy sensor nodes at the current moment, multiplies them respectively by a weighting constant derived from the inverse normalization of the straight-line distance, and sums them, using the calculated value directly as the alternative estimate. This logic does not rely on mathematical prediction models with high computational overhead. It leverages the physical characteristics of hardware equipotentiality—where closer the spatial distance and the more consistent the RF power density and DC dissipation—to achieve high-precision hardware parameter reconstruction with lower microcontroller clock cycle usage, thus blocking the triggering process of closed-loop calculation failure caused by a single component failure. The above-mentioned hardware component combination relationship and the associated signal monitoring, algorithm judgment, and hierarchical control process collectively constitute the implementation method of the pulse radiator described in this application.

[0078] Obviously, those skilled in the art can make various modifications and variations to this invention without departing from its spirit and scope. Therefore, if these modifications and variations fall within the scope of the claims of this invention and their equivalents, this invention also intends to include these modifications and variations.

Claims

1. A pulse radiator, comprising a radio frequency multi-stage amplification link and a measurement and control communication component; the radio frequency multi-stage amplification link generates an output pulse signal; the measurement and control communication component is configured to perform real-time monitoring and feedback control of the radio frequency multi-stage amplification link; Its features are, The measurement and control communication component is configured with an adaptive degradation and fault-prevention shutdown control strategy. The execution steps of the adaptive degradation fault-prevention shutdown control strategy include: In continuous radiation mode, the operating status parameters of the radio frequency multi-stage amplification link are continuously acquired; When the operating status parameters reach the preset warning limit, the measurement and control communication component triggers adaptive degradation control, which reduces the output gain of the radio frequency multi-stage amplification link by issuing a dynamic attenuation control code, thus triggering entry into the degradation operation mode. During the degraded operation mode, the development trend of the operation status parameters is continuously monitored; When the operating status parameters return to the safe range, the measurement and control communication component reverses the dynamic attenuation control code, so that the output gain of the RF multi-stage amplification link smoothly returns to the initial setting state.

2. The pulse radiator according to claim 1, characterized in that, The RF multi-stage amplification link includes a pre-stage driver component, a secondary driver component, and a final stage synthesizer component; the pre-stage driver component integrates an electrically adjustable attenuator. The attenuation of the electrically adjustable attenuator is controlled by the measurement and control communication component; The final-stage synthesis component includes a microstrip power divider synthesis module and a waveguide power divider synthesis module.

3. The pulse radiator according to claim 2, characterized in that, The output of the radio frequency multi-stage amplification link is equipped with a forward coupler, a reverse coupler, and a detector. The operating status parameters monitored by the measurement and control communication component include forward detection voltage and reverse detection voltage; The detector includes a forward detection branch and a reverse detection branch; both the forward and reverse detection branches include a broadband envelope detector diode network and a temperature compensation impedance unit; the temperature compensation impedance unit includes a DC bias compensation network composed of a negative temperature coefficient thermistor and a metal film resistor, wherein the negative temperature coefficient thermistor and the broadband envelope detector diode network are closely mounted and share the same copper-plated grounded thermal conductive area.

4. The pulse radiator according to claim 3, characterized in that, The measurement and control communication component acquires externally input frequency data, determines the corresponding target detection voltage based on the mapping relationship, and then enters the closed-loop automatic level control process. In the closed-loop automatic level control process, the measurement and control communication component dynamically adjusts the attenuation value of the electrically adjustable attenuator to ensure that the positive detection voltage matches the target detection voltage.

5. The pulse radiator according to claim 4, characterized in that, The pulse radiator also includes a power switch control circuit. The measurement and control communication component is connected to the power switch control circuit; When the operating status parameters exceed the limit protection threshold, the measurement and control communication component sends a power-off control signal to the power switch control circuit to block the power supply to the radio frequency multi-stage amplification link.

6. The pulse radiator according to claim 4, characterized in that, The radio frequency multi-stage amplification link includes multiple parallel amplification modules; When the power supply current imbalance of the multi-channel parallel amplifier module exceeds the preset alarm threshold, the measurement and control communication component triggers the adaptive degradation control and suspends the execution of the closed-loop automatic level control process.

7. The pulse radiator according to claim 6, characterized in that, During the adaptive degradation control process, the measurement and control communication component also acquires the internal module temperature rise rate; when both the internal module temperature rise rate and the reverse detector voltage rise rate exceed the preset rate benchmark, the measurement and control communication component reconstructs the dynamic attenuation control code and synchronously reduces the duty cycle of the pulse excitation signal of the internal digital pulse modulation generator to reduce microwave peak heat dissipation.

8. The pulse radiator according to claim 7, characterized in that, After entering the degraded operation mode, the system is in a low-power safety maintenance state; When in the low-power safety maintenance state, the measurement and control communication component recalculates and maps the degraded target detection voltage based on the real-time ratio of the forward detection voltage to the reverse detection voltage, thereby maintaining the continuous radiation of the radio frequency pulse signal.

9. The pulse radiator according to claim 7, characterized in that, The measurement and control communication component is provided with limiting conditions to activate the reverse adjustment and recovery mechanism; the limiting conditions include: the internal module temperature rise rate turns into a negative value and the absolute value remains stable, while the real-time temperature of the internal module obtained by the sensor falls back to below the preset safe temperature limit, and the power supply current imbalance falls back to below the preset warning limit, and no longer fluctuates within the preset time window.

10. The pulse radiator according to claim 9, characterized in that, During the reverse adjustment of the dynamic attenuation control code, the measurement and control communication component gradually reduces the attenuation of the electrically adjustable attenuator; after each reduction in attenuation, the power supply current imbalance is continuously checked. When the output gain of the RF multi-stage amplification link returns to the initial set state, the measurement and control communication component resumes the closed-loop automatic level control process.

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