Metering equipment remote calibration method and device, medium and equipment

Abstract

The invention discloses a metering equipment remote calibration method and device, a medium and equipment. The method comprises the following steps: calculating a loss index according to current characteristics of an extracted current signal in a monitoring period, and determining a phase offset of each harmonic based on the loss index; constructing an environment gain coefficient according to the environment temperature and the environment humidity in the environment management period; constructing a current correction coefficient according to the fundamental wave amplitude of the current signal in the monitoring period and the environment gain coefficient; and correcting each harmonic amplitude in the next monitoring period according to the current correction coefficient, and correcting each harmonic phase in the next monitoring period according to the phase offset of each harmonic to obtain a calibration current in the next monitoring period.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of power test equipment, and more particularly, to a metering equipment remote calibration method, device, medium and equipment. BACKGROUND

[0002] The existing remote calibration technology of power test equipment mainly relies on fixed period compensation and temperature rise linear prediction model, which is difficult to adapt to complex working conditions such as possible superimposition of high-order harmonics (2kHz-20kHz) and sudden temperature change (-10℃-50℃) under different calibration environments.

[0003] Specifically, in the remote calibration process of power metering equipment (such as a mutual inductor calibrator), high-order harmonics will interfere with its signal acquisition and error calculation accuracy, and the traditional linear prediction model cannot dynamically match the magnetic core loss and phase shift characteristics under the harmonic environment, resulting in cumulative calibration errors over time. In addition, the temperature and humidity compensation mechanism based on empirical formula has a response lag when the metering equipment faces a near dew point, conductor dewing and other metastable states, especially when the internal insulation material of the equipment has a micro-discharge phenomenon due to sudden humidity change, which easily aggravates the time-varying error of the internal measurement loop, directly affecting the accuracy of the remote calibration of the metering equipment.

[0004] Such technical defects are essentially due to the fact that the existing methods do not fully consider the dynamic characteristics of power test equipment in a multi-physical field (electromagnetic-thermal-humidity field) coupled environment, so it is necessary to establish a multi-physical field dynamic coupling high-robustness calibration method suitable for the remote calibration requirements of metering equipment to solve the calibration accuracy degradation problem under complex working conditions. SUMMARY

[0005] In view of the deficiencies of the prior art, the present application provides a metering equipment remote calibration method, device, medium and equipment.

[0006] According to one aspect of the present application, a metering equipment remote calibration method is provided, comprising:

[0007] calculating a loss index according to the current characteristics of the current signal in the extracted monitoring period, and determining the phase shift amount of each harmonic based on the loss index;

[0008] constructing an environmental gain coefficient according to the environmental temperature and the environmental humidity in the environmental management period;

[0009] constructing a current correction coefficient according to the fundamental wave amplitude of the current signal in the monitoring period and the environmental gain coefficient;

[0010] correcting the amplitude of each harmonic in the next monitoring period according to the current correction coefficient, and correcting the phase of each harmonic in the next monitoring period according to the phase shift amount of each harmonic, to obtain the calibration current of the next monitoring period.

[0011] Optionally, the loss index is calculated according to the current characteristic of the extracted current signal in the monitoring period, comprising:

[0012] The current signal in the monitoring period is collected;

[0013] The amplitude of each harmonic of the current signal is extracted by using the fast Fourier transform method;

[0014] The magnetic induction intensity is calculated according to the amplitude of each harmonic and the transformer ratio coefficient;

[0015] The loss index is calculated according to the magnetic induction intensity.

[0016] Optionally, the calculation expression of the loss index is:

[0017]

[0018] In the formula, P is the loss index, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, fn is the frequency index, fn=n*50Hz; Bn is the magnetic induction intensity of the n-th harmonic.

[0019] Optionally, the phase shift amount of each harmonic is determined based on the loss index, comprising:

[0020] The voltage effective value of the n-th harmonic of the current signal is extracted;

[0021] The equivalent resistance of the n-th harmonic is calculated according to the voltage effective value and the loss index;

[0022] The phase shift amount of the n-th harmonic is calculated according to the equivalent resistance of the n-th harmonic, the transformer excitation inductance, and the frequency index.

[0023] Optionally, the calculation expression of the equivalent resistance is:

[0024] Rn=Vn 2 / P

[0025] In the formula, Vn is the voltage effective value; P is the loss index;

[0026] The calculation expression of the phase shift amount θn is:

[0027] θn=arctan(2×π×fn×L / Rn)

[0028] In the formula, θn is the n-th harmonic shift amount; fn is the frequency index; L is the transformer excitation inductance.

[0029] Optionally, the environmental gain coefficient is constructed according to the ambient temperature and the ambient humidity in the monitoring period, comprising:

[0030] The environmental temperature threshold is calculated according to the ambient temperature and the ambient humidity;

[0031] The water vapor state is determined according to the environmental temperature threshold and the environmental humidity, and the environmental gain coefficient is constructed according to the water vapor state.

[0032] Optionally, the calculation expression of the environmental temperature threshold is:

[0033]

[0034] In the formula, Y is the environmental temperature threshold, β1 is a temperature offset coefficient, β2 is a temperature empirical constant, t is the environmental temperature, and s is the environmental humidity.

[0035] Optionally, the water vapor state is determined according to the environmental temperature threshold and the environmental humidity, and the environmental gain coefficient is constructed according to the water vapor state, including:

[0036] In the case that the environmental temperature is less than or equal to T+2 and the environmental humidity is greater than or equal to a preset humidity threshold s1, it is determined that the water vapor state is an abnormal state, and the environmental gain coefficient is constructed as [1+γ×(s-s1)], where γ is an adjustment factor; otherwise, it is determined that the water vapor state is a normal state, and the environmental gain coefficient is constructed as 1.

[0037] Optionally, the method further includes: updating the environmental gain coefficient according to a protective ring capacitance change state in an environmental management period.

[0038] Optionally, the environmental gain coefficient is updated according to a protective ring capacitance change state in an environmental management period, including:

[0039] The protective ring capacitance change rate BH=|D1-D2| / (D2×△t) is calculated according to the protective ring capacitance D1 collected in the environmental management period and the protective ring capacitance D2 collected in the last environmental management period, where △t is the length of the environmental management period;

[0040] If the protective ring capacitance change rate BH is greater than a preset change rate threshold b0, the environmental gain coefficient is updated as {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is an update coefficient, and HK is the environmental gain coefficient before the update; otherwise, the environmental gain coefficient is not updated.

[0041] Optionally, the current correction coefficient is constructed according to the fundamental wave amplitude of the current signal in the monitoring period and the environmental gain coefficient, including:

[0042] The current correction weight factor is determined according to the fundamental wave amplitude of the current signal in the monitoring period;

[0043] The current correction coefficient is constructed according to the current correction weight factor and the environmental gain coefficient.

[0044] Optionally, the expression of the current correction weight factor is:

[0045]

[0046] In the formula, W is a current correction weight factor, F1 is a fundamental amplitude in a monitoring period; Fn is an n-th harmonic amplitude.

[0047] Optionally, the current correction coefficient is constructed according to the current correction weight shadow and the environmental gain coefficient, and the current correction coefficient comprises:

[0048] When the current correction weight factor is less than or equal to a compensation threshold r0, the current correction coefficient is constructed as [z1×(1-0.1×W)×environmental gain coefficient], otherwise the current correction coefficient is constructed as [z2×(1-0.1×W)×environmental gain coefficient], wherein z1 is a first compensation factor and z2 is a second compensation factor.

[0049] Optionally, each harmonic amplitude Fnj of the calibration current is Fnj×current correction coefficient, wherein Fnj is a measurement value of the n-th harmonic amplitude in a next monitoring period.

[0050] The phase of each harmonic of the calibration current is θn is a measurement value of the n-th harmonic phase in a next monitoring period; θn is an n-th harmonic offset.

[0051] According to another aspect of the present application, a metering device remote calibration device is provided, comprising:

[0052] A calculation module is configured to calculate a loss index according to the extracted current characteristics of the current signal in the monitoring period, and determine the phase offset of each harmonic based on the loss index;

[0053] A first construction module is configured to construct an environmental gain coefficient according to the environmental temperature and the environmental humidity in an environmental management period;

[0054] A second construction module is configured to construct a current correction coefficient according to the fundamental amplitude of the current signal in the monitoring period and the environmental gain coefficient;

[0055] A correction module is configured to correct each harmonic amplitude in a next monitoring period according to the current correction coefficient, and correct the phase of each harmonic in the next monitoring period according to the phase offset of each harmonic, so as to obtain the calibration current in the next monitoring period.

[0056] According to still another aspect of the present application, a computer readable storage medium is provided, the storage medium stores a computer program, and the computer program is used to execute the method of any one of the above aspects of the present application.

[0057] According to a further aspect of the present application, there is provided an electronic device comprising: a processor; a memory for storing processor-executable instructions; the processor being arranged to read the executable instructions from the memory and execute the instructions to implement the method of any one of the above aspects of the present application.

[0058] Thus, the present application realizes accurate compensation of high-frequency signal amplitude and phase in the full frequency band by analyzing the harmonic energy loss and the nonlinear transformation law of the core; a prediction formula adjustment system of the environmental gain coefficient is constructed by combining the composite sensing mechanism of temperature and humidity-protection ring state, effectively breaking through the inherent deviation of the linear temperature drift model; relying on the closed-loop hierarchical verification architecture generated by dynamic weight, both fast calibration response and long-term error stability control are taken into account. Compared with the traditional method, the measurement distortion problem induced by harmonic group distortion and alternating heat and humidity is systematically solved, and the energy efficiency measurement reliability and equipment life cycle management efficiency under complex working conditions are significantly improved. BRIEF DESCRIPTION OF DRAWINGS

[0059] The exemplary embodiments of the present application will be more fully understood from the following drawings, in which:

[0060] Figure 1 is a flowchart of a remote calibration method of a measurement device provided by an exemplary embodiment of the present application;

[0061] Figure 2 is a structural schematic diagram of a remote calibration device of a measurement device provided by an exemplary embodiment of the present application;

[0062] Figure 3 is a structure of an electronic device provided by an exemplary embodiment of the present application. DETAILED DESCRIPTION

[0063] Hereinafter, exemplary embodiments according to the present application will be described in detail with reference to the accompanying drawings. Obviously, the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments of the present application, and it should be understood that the present application is not limited to the exemplary embodiments described herein.

[0064] It should be noted that: unless otherwise specified, the relative arrangement, numerical expression and numerical value of the components and steps set forth in these embodiments do not limit the scope of the present application.

[0065] Those skilled in the art can understand that the terms "first", "second" and the like in the embodiments of the present application are only used to distinguish different steps, devices or modules, and do not represent any specific technical meaning, nor do they represent the inevitable logical sequence between them.

[0066] It should also be understood that in the embodiments of the present application, "a plurality of" can mean two or more, and "at least one" can mean one, two or more.

[0067] It should also be understood that, whenever used in the present disclosure, the terms "comprise", "comprising", "comprises", "include", "including", "includes", "have", "has", "having", or "contains" or "containing", or any other variation thereof, shall not be a limitation, and should be understood to imply the inclusion of an item or items, but not to the exclusion of any other item or items. It should further be noted that the terms "comprise", "comprising", "comprises", "include", "including", "includes", "have", "has", "having", or "contains" or "containing" or any other variation thereof, are not intended to exclude any additional, optional, or optional components or steps.

[0068] In addition, the term "and / or" in the present application is merely used to describe associated objects, and can represent three relationships, for example, A and / or B can represent three cases of A alone, A and B together, and B alone. In addition, the character " / " in the present application generally represents an "or" relationship between the front and rear associated objects.

[0069] It should also be understood that the description of the present application focuses on the differences between various embodiments, and the same or similar parts can be referred to each other, and for the sake of brevity, will not be repeated.

[0070] At the same time, it should be understood that, for the convenience of description, the size of each part shown in the drawings is not drawn according to the actual proportion relationship.

[0071] The following description of at least one example embodiment is merely illustrative in nature and is in no way intended to limit the application or its application or use.

[0072] Techniques, methods, and devices known to those of ordinary skill in the relevant art can not be discussed in detail, but where appropriate, the techniques, methods, and devices should be considered as part of the specification.

[0073] It should be noted that: similar signs and letters represent similar items in the following drawings, so once an item is defined in one drawing, it does not need to be further discussed in subsequent drawings.

[0074] Embodiments of the present application can be applied to terminal devices, computer systems, servers and other electronic devices, which can operate with many other general or special computing system environments or configurations. Examples of well-known terminal devices, computing systems, environments, and / or configurations suitable for use with terminal devices, computer systems, servers and other electronic devices include, but are not limited to: personal computer systems, server computer systems, thin clients, thick clients, handheld or laptop devices, microprocessor-based systems, set-top boxes, programmable consumer electronics, network personal computers, small computer systems, mainframe computer systems, and distributed cloud computing technology environments including any of the above systems, etc.

[0075] Electronic devices such as terminal devices, computer systems, servers, and the like can be described in the general context of computer system-executable instructions, such as program modules, being executed by a computer system. Generally, program modules can include routines, programs, objects, components, logic, data structures, and the like that perform particular tasks or implement particular abstract data types. Computer systems / server can be practiced in distributed cloud computing environments with other computer systems coupled via communication networks. The program modules can be stored in the local or remote computer system memory devices.

[0076] Exemplary method

[0077] Figure 1 is a flowchart of a meter remote calibration method provided by an exemplary embodiment of the present application. The embodiment can be applied to electronic devices, such as Figure 1 As shown, the meter remote calibration method 100 includes the following steps:

[0078] Step 101, calculating a loss index according to the current characteristics of the current signal in the extracted monitoring period, and determining the phase offset of each harmonic based on the loss index;

[0079] Step 102, constructing an environmental gain coefficient according to the environmental temperature and the environmental humidity in the environmental management period;

[0080] Step 103, constructing a current correction coefficient according to the fundamental wave amplitude of the current signal in the monitoring period and the environmental gain coefficient;

[0081] Step 104, correcting the amplitude of each harmonic in the next monitoring period according to the current correction coefficient, and correcting the phase of each harmonic in the next monitoring period according to the phase offset of each harmonic, to obtain the calibration current of the next monitoring period.

[0082] The embodiment is aimed at the distributed photovoltaic metering scene with superimposed high-order harmonics and strong environmental disturbance, and proposes a remote calibration method based on harmonic iron loss-phase coupling modeling and multi-parameter dynamic compensation. Specifically, it includes:

[0083] Step S101, collecting the current signal and the voltage signal of the target.

[0084] Specifically, the target described in the embodiment is a transformer calibrator, and those skilled in the art can set the target to be a power test related device with metering function.

[0085] Exemplarily, in the embodiment, an AD7606-8 channel 16-bit ADC chip can be used to synchronously collect three-phase voltage and current, the sampling rate is fixed at 10 kHz, it is ensured that the fundamental wave and 2-50th harmonic waves are decomposed through an FFT module of an ADSP-BF707 processor, and the data collection manner is not specifically limited in the embodiment, and a person skilled in the art can freely set it according to the requirement.

[0086] In step S102, the current characteristics are extracted according to the current signal in the monitoring period to determine the loss index, and the phase shift amount of each harmonic wave is determined according to the loss index.

[0087] Specifically, the influence of the harmonic loss on the performance of the core is quantified, the phase lag effect of each harmonic wave is accurately modeled, the nonlinear error of the mutual inductor under high-frequency working conditions can be corrected in a targeted manner, and the measurement integrity of the harmonic component is fundamentally improved. The method solves the defect of the traditional scheme that simplifies the harmonic as amplitude superposition.

[0088] Step S102 includes:

[0089] In step S201, the current characteristics are extracted according to the current signal in the monitoring period to determine the loss index.

[0090] Specifically, the amplitudes of the harmonic waves of the current signal in the monitoring period are extracted according to the fast Fourier transform, the amplitude of the nth harmonic wave is denoted as Fn, the product of Fn and the proportional coefficient h of the mutual inductor is taken as the magnetic induction intensity corresponding to the amplitude of the nth harmonic wave, and the loss index is calculated. The expression of the loss index is:

[0091]

[0092] In the formula, P is the loss index, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, fn is the frequency index, and fn=n*50Hz.

[0093] Specifically, the influence of the iron loss on the transmission characteristic is quantitatively restored through the coupling modeling of the harmonic magnetic induction intensity and the frequency parameter, and an explicit physical basis is provided for the compensation strategy, which overcomes the limitation that the empirical formula depends on the measured data.

[0094] Exemplarily, in the embodiment, the monitoring period can be set to 1 minute, and the setting of the monitoring period is not specifically limited in the embodiment, and a person skilled in the art can freely set it according to the requirement.

[0095] Exemplarily, in the embodiment, the fast Fourier transform can be used to perform the spectrum analysis on the sampling signal, the amplitude of the harmonic frequency point is directly located from the spectrum, and the effective value voltage of the harmonic is obtained by dividing the read harmonic amplitude by the square root of 2; Exemplarily, in the embodiment, the collection mode of the amplitude of each harmonic and the corresponding effective value voltage is not specifically limited, and a person skilled in the art can freely set according to the needs.

[0096] Exemplarily, in the embodiment, the hysteresis loss coefficient can be set to 3.2×10 -5 W / (T 1.6 ·Hz), the eddy current loss coefficient can be set to 8.9×10 -7 W / (T 2 ·Hz 2 ), and the mutual inductance ratio coefficient can be set to 10 -3 T / A. The hysteresis loss coefficient, the eddy current loss coefficient and the mutual inductance ratio coefficient in the embodiment can be obtained by interaction, and a person skilled in the art can set according to the nameplate parameters of the mutual inductor.

[0097] Step S202, determining the phase shift of each harmonic according to the loss index.

[0098] Specifically, the voltage effective value of the nth harmonic is extracted as Vn, and the equivalent resistance Rn corresponding to the nth harmonic is calculated according to Vn and the loss index P. The expression of the equivalent resistance Rn corresponding to the nth harmonic is: Rn=Vn 2 / P;

[0099] The equivalent resistance Rn corresponding to the nth harmonic, the excitation inductance L of the mutual inductor and the frequency index fn are fused to determine the phase shift of the nth harmonic. The expression of the phase shift of the nth harmonic is:

[0100] θn=arctan(2×π×fn×L / Rn).

[0101] Specifically, the phase lag angle is inversely calculated based on the equivalent resistance and the inductance characteristics, the analytical relationship between the magnetic core material characteristics and the measurement error is revealed, the phase calibration parameters have clear boundary condition constraints, and the divergence problem caused by the traditional phase compensation due to frequency extrapolation is avoided.

[0102] Exemplarily, in the embodiment, the acquisition mode of the excitation inductance of the mutual inductor is not specifically limited, and a person skilled in the art can freely set according to the needs, such as the excitation inductance of the mutual inductor can be obtained by interaction.

[0103] Step S103, calculating the environment temperature threshold according to the environment temperature and the environment humidity collected in the environment management period, and judging the water vapor state according to the environment temperature threshold and the environment humidity to construct the environment gain coefficient, wherein the environment temperature is the temperature in the electric meter box, and the environment humidity is the environment humidity where the electric meter box is located.

[0104] Specifically, the environment temperature threshold is calculated based on the environment temperature t and the environment humidity s collected in the environment management period, and the expression of the environment temperature threshold is as follows:

[0105]

[0106] In the formula, Y is the environment temperature threshold, β1 is the temperature offset coefficient, and β2 is the temperature empirical constant.

[0107] When the environment temperature t is less than or equal to (the environment temperature threshold Y+2) and the environment humidity s is greater than or equal to the humidity threshold s1, it is determined that the water vapor state in the current management period is an abnormal state, and the environment gain coefficient is constructed as [1+γ×(s-s1)], wherein γ is the adjustment factor; otherwise, it is determined that the water vapor state in the current management period is a normal state, and the environment gain coefficient is constructed as 1.

[0108] Specifically, the traditional single temperature and humidity monitoring is upgraded to a joint prediction system of the environment safety domain by introducing the dew point temperature threshold mechanism. The mechanism can dynamically determine the cooperative risk of the temperature and humidity in the electric meter box, and construct the environment gain coefficient matrix based on the adjustment factor to realize the hierarchical control of the compensation strength. This method not only can block the insulation deterioration process caused by humidity penetration, but also can compensate the reference voltage temperature drift in a nonlinear manner for sub-stable working conditions, effectively reducing the high-frequency oscillation error caused by environmental mutations. At the same time, through the time sequence control of the environment management period, the update of the gain coefficient has both fast response and parameter stability.

[0109] For example, in the present embodiment, the environment management period can be set to 0.25h, and in the present embodiment, the setting of the environment management period is not specifically limited, and a person skilled in the art can freely set it according to the needs.

[0110] For example, in the present embodiment, the temperature offset coefficient can be set to 237.3, the temperature empirical constant can be set to 17.27, the humidity threshold can be set to 75, and the adjustment factor can be set to 0.003, and in the present embodiment, the above settings are not specifically limited, and a person skilled in the art can freely set them according to the needs.

[0111] For example, in the present embodiment, the environment temperature can be obtained by a temperature sensor, and the environment humidity can be obtained by a humidity sensor, and in the present embodiment, the acquisition method of the environment temperature and the environment humidity is not specifically limited, and a person skilled in the art can freely set it according to the needs.

[0112] Specifically, in the embodiment, the unit of the ambient temperature is ℃, the unit of the ambient humidity is %, only the value is considered when calculating, and the unit is not considered, the ambient temperature and the ambient humidity are collected at the beginning of the environmental management period, and the construction of the ambient gain coefficient is also constructed at the beginning of the environmental management period.

[0113] In step S104, the guard ring capacitance change state is determined according to the guard ring capacitance collected in the environmental management period, and the ambient gain coefficient is updated based on the guard ring capacitance change state. The guard ring is a ring-shaped conductor wrapped outside the measurement loop, and the guard ring capacitance refers to the parasitic capacitance between the target guard ring and the adjacent conductor structure.

[0114] Specifically, the guard ring capacitance D1 collected in the environmental management period and the guard ring capacitance D2 collected in the last environmental management period are used to calculate the guard ring capacitance change rate BH, BH = |D1-D2| / (D2×△t),△t is the length of the environmental management period, if BH is greater than the change rate threshold b0, the ambient gain coefficient is updated to {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, η is the update coefficient, if BH is less than or equal to the change rate threshold b0, the ambient gain coefficient is not updated, and HK is the ambient gain coefficient before updating.

[0115] Specifically, by monitoring the dynamic change of the parasitic capacitance between the guard ring and the adjacent conductor, the abnormality of the capacitance medium caused by external pollution, mechanical deformation or contact oxidation is indirectly perceived. This method solves the defect that conventional environmental sensors can only detect macroscopic temperature and humidity and cannot capture the microstate change of the conductor surface. It is especially suitable for early warning of hidden interference caused by dust and rust accumulation on long-term outdoor equipment. Combined with the gradient threshold of the capacitance change rate, the slow degradation and sudden change of the pressure change scene can be accurately identified, and then a segmented gain correction strategy is adopted: logarithmic smoothing compensation is loaded for chronic deviation to maintain stability, and rapid response suppression is applied to sudden interference to block error chain diffusion, which significantly improves the robustness of the measurement system in complex contaminated environments.

[0116] For example, in the embodiment, the change rate threshold can be set to 0.1% / h, the update coefficient can be set to 0.12, and the update coefficient can be set to 0.05. In the embodiment, the above settings are not specifically limited, and those skilled in the art can freely set them according to the needs.

[0117] For example, in the embodiment, the guard ring capacitance can be collected by a capacitance measurement chip

[0118] In step S105, the current correction coefficient is determined according to the extraction result of the current characteristic in the monitoring period and the ambient gain coefficient, and the amplitude and phase of each harmonic are corrected based on the current correction coefficient and the phase offset of each harmonic.

[0119] Step S105 comprises:

[0120] Step S501, according to the extraction result of the current characteristic in the monitoring period, determine the current correction weight factor, and construct the current correction coefficient based on the current correction weight factor and the environmental gain coefficient.

[0121] Specifically, the expression of the current correction weight factor is:

[0122]

[0123] In the formula, W is the current correction weight factor, F1 is the fundamental amplitude in the monitoring period;

[0124] Based on the current correction weight factor W, the current correction coefficient is constructed. When the current correction weight factor is less than or equal to the compensation threshold r0, the current correction coefficient is set to [z1×(1-0.1×W)×environmental gain coefficient], and when the current correction weight factor is greater than the compensation threshold r0, the current correction coefficient is set to [z2×(1-0.1×W)×environmental gain coefficient];

[0125] Wherein, z1 is the first compensation factor, and z2 is the second compensation factor.

[0126] Specifically, the segmented correction coefficient is constructed in combination with the environmental gain and the harmonic characteristic, which allows adaptive adjustment of the compensation strength under different working conditions, ensuring the measurement smoothness under the steady state condition and quickly converging the error in the transient disturbance.

[0127] For example, in the present embodiment, the compensation threshold can be set to 0.1, the first compensation factor can be set to 0.98, and the second compensation factor can be set to 0.95. The above settings are not specifically limited in the present embodiment, and can be freely set by those skilled in the art according to the requirements.

[0128] Step S502, according to the current correction coefficient, correct the harmonic amplitude of the next monitoring period, and according to the phase shift of each harmonic, correct the phase of each harmonic of the next monitoring period.

[0129] Specifically, the n-th harmonic amplitude of the next monitoring period is corrected to Fnjj, Fnjj=Fnj×current correction coefficient, Fnj is the measured value of the n-th harmonic amplitude of the next monitoring period;

[0130] The n-th harmonic phase of the next monitoring period is corrected to is the measured value of the n-th harmonic phase of the next monitoring period.

[0131] Specifically, through the closed-loop recursive mechanism of "measurement-feature extraction-parameter update", the dynamic tracking of error correction is realized, the continuity of parameters across monitoring periods is ensured, and the periodic error fluctuation caused by the lag of calibration parameters is significantly reduced.

[0132] Specifically, the first harmonic in the embodiment is the fundamental wave.

[0133] Therefore, the present application realizes accurate compensation of the amplitude and phase of high-frequency signals in the full frequency band by analyzing the harmonic energy loss and the nonlinear transformation law of the core; combined with the composite sensing mechanism of temperature and humidity-protection ring state, a predictive adjustment system of environmental gain coefficient is constructed, effectively breaking through the inherent deviation of the linear temperature drift model; relying on the closed-loop recursive verification architecture generated by dynamic weight, both fast calibration response and long-term error stability control are considered. Compared with the traditional method, the distortion problem of harmonic group distortion and alternating heat and humidity induced measurement distortion is systematically solved, and the reliability of energy efficiency measurement and the efficiency of equipment life cycle management under complex working conditions are significantly improved.

[0134] Exemplary apparatus

[0135] Figure 2 is a structural schematic diagram of a remote calibration device for a metering equipment provided by an exemplary embodiment of the present application. As shown in Figure 2 , the device 200 includes:

[0136] The calculation module 210 is configured to calculate a loss index according to the current characteristics of the current signal in the monitoring period, and determine the phase offset of each harmonic based on the loss index.

[0137] The first construction module 220 is configured to construct an environmental gain coefficient according to the environmental temperature and the environmental humidity in the environmental management period.

[0138] The second construction module 230 is configured to construct a current correction coefficient according to the fundamental wave amplitude of the current signal in the monitoring period and the environmental gain coefficient.

[0139] The correction module 240 is configured to correct the amplitude of each harmonic in the next monitoring period according to the current correction coefficient, and correct the phase of each harmonic in the next monitoring period according to the phase offset of each harmonic, to obtain the calibration current of the next monitoring period.

[0140] Optionally, the calculation module 210 calculates the loss index according to the current characteristics of the current signal in the monitoring period, including:

[0141] The acquisition sub-module is configured to acquire the current signal in the detection period.

[0142] The extraction sub-module is configured to extract the amplitude of each harmonic of the current signal by using the fast Fourier transform method.

[0143] The first calculation sub-module is configured to calculate the magnetic induction intensity according to the amplitude of each harmonic and the transformer proportional coefficient;

[0144] The second calculation sub-module is configured to calculate the loss index according to the magnetic induction intensity.

[0145] Optionally, the calculation expression of the loss index is as follows:

[0146]

[0147] In the formula, P is the loss index, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, fn is the frequency index, fn = n x 50 Hz, and Bn is the magnetic induction intensity of the n-th harmonic.

[0148] Optionally, the calculation of the phase shift of each harmonic based on the loss index in the calculation module 210 comprises:

[0149] extracting the voltage effective value of the n-th harmonic of the current signal;

[0150] calculating the equivalent resistance of the n-th harmonic according to the voltage effective value and the loss index;

[0151] calculating the phase shift of the n-th harmonic according to the equivalent resistance of the n-th harmonic, the transformer excitation inductance, and the frequency index.

[0152] Optionally, the calculation expression of the equivalent resistance is as follows:

[0153] Rn = Vn 2 / P

[0154] In the formula, Vn is the voltage effective value, and P is the loss index.

[0155] The calculation expression of the phase shift θn is as follows:

[0156] θn = arctan (2 x π x fn x L / Rn)

[0157] In the formula, θn is the phase shift of the n-th harmonic, fn is the frequency index, and L is the transformer excitation inductance.

[0158] Optionally, the first construction module 220 comprises:

[0159] calculating the environmental temperature threshold according to the environmental temperature and the environmental humidity;

[0160] determining the water vapor state according to the environmental temperature threshold and the environmental humidity, and constructing the environmental gain coefficient according to the water vapor state.

[0161] Optionally, the calculation expression of the environmental temperature threshold is as follows:

[0162]

[0163] In the formula, Y is an ambient temperature threshold, β1 is a temperature offset coefficient, β2 is a temperature empirical constant; t is an ambient temperature, and s is an ambient humidity.

[0164] Optionally, the water vapor state is determined according to the ambient temperature threshold and the ambient humidity, and the ambient gain coefficient is constructed according to the water vapor state, including:

[0165] In a case where the ambient temperature is less than or equal to T+2 and the ambient humidity is greater than or equal to a preset humidity threshold s1, it is determined that the water vapor state is an abnormal state, and the ambient gain coefficient is constructed as [1+γ×(s-s1)], where γ is an adjustment factor; otherwise, it is determined that the water vapor state is a normal state, and the ambient gain coefficient is constructed as 1.

[0166] Optionally, the device 200 further includes an updating module configured to update the ambient gain coefficient according to a change state of the guard ring capacitance in an environmental management period.

[0167] Optionally, the updating module includes:

[0168] The guard ring capacitance change rate BH=|D1-D2| / (D2×△t) is calculated according to the guard ring capacitance D1 collected in the environmental management period and the guard ring capacitance D2 collected in the last environmental management period, where △t is the length of the environmental management period;

[0169] If the guard ring capacitance change rate BH is greater than a preset change rate threshold b0, the ambient gain coefficient is updated as {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is an updating coefficient, and HK is the ambient gain coefficient before updating; otherwise, the ambient gain coefficient is not updated.

[0170] Optionally, the second construction module 230 includes:

[0171] The current correction weight factor is determined according to the fundamental wave amplitude of the current signal in the monitoring period;

[0172] The current correction coefficient is constructed according to the current correction weight shadow and the ambient gain coefficient.

[0173] Optionally, the expression of the current correction weight factor is:

[0174]

[0175] In the formula, W is the current correction weight factor, F1 is the fundamental wave amplitude in the monitoring period, and Fn is the n-th harmonic amplitude.

[0176] Optionally, the current correction coefficient is constructed according to the current correction weight shadow and the ambient gain coefficient, including:

[0177] When the current correction weight factor is less than or equal to a compensation threshold r0, a current correction coefficient is constructed as [z1×(1-0.1×W)×ambient gain coefficient], otherwise the current correction coefficient is constructed as [z2×(1-0.1×W)×ambient gain coefficient], wherein z1 is a first compensation factor and z2 is a second compensation factor.

[0178] Optionally, the harmonic amplitude Fnj of the calibration current is Fnj×current correction coefficient, wherein Fnj is a measurement value of the harmonic amplitude of the next monitoring period n.

[0179] The harmonic phase of the calibration current is is a measurement value of the harmonic phase of the next monitoring period n, and θn is the harmonic offset.

[0180] Exemplary electronic device

[0181] Figure 3 is a structure of an electronic device provided by an exemplary embodiment of the present application. As shown in Figure 3 the electronic device 30 includes one or more processors 31 and a memory 32.

[0182] The processor 31 can be a central processing unit (CPU) or other form of processing unit that has data processing capability and / or instruction execution capability, and can control other components in the electronic device to perform desired functions.

[0183] The memory 32 can include one or more computer program products that can include various forms of computer readable storage media, such as volatile memory and / or non-volatile memory. The volatile memory, for example, can include random access memory (RAM), cache memory, and / or the like. The non-volatile memory, for example, can include read only memory (ROM), hard disk, flash memory, and / or the like. One or more computer program instructions can be stored on the computer readable storage media, and the processor 31 can execute the program instructions to implement the methods of the software programs of the various embodiments of the present application described above and / or other desired functions. In one example, the electronic device can further include an input device 33 and an output device 34, and these components are interconnected by a bus system and / or other form of connection mechanism (not shown).

[0184] In addition, the input device 33 can further include, for example, a keyboard, a mouse, and / or the like.

[0185] The output device 34 can output various information to the outside. The output device 34 can include, for example, a display, a speaker, a printer, a communication network and a remote output device connected thereto, and / or the like.

[0186] Of course, in order to simplify, Figure 3 Only some of the components in the electronic device related to the present application are shown in FIG. 1, and components such as buses, input / output interfaces, etc. are omitted. In addition to this, the electronic device can include any other appropriate components according to a specific application.

[0187] Exemplary computer program product and computer readable storage medium

[0188] In addition to the above-mentioned methods and devices, embodiments of the present application can also be a computer program product including computer program instructions, which, when executed by a processor, cause the processor to perform steps of the methods according to various embodiments of the present application described in the above "Exemplary Methods" section of the specification.

[0189] The computer program product can be written in any combination of one or more programming languages, including an object oriented programming language such as Java, C++, etc., and conventional procedural programming languages, such as the "C" programming language or similar programming languages. The program code can execute entirely on the user's computing device, partly on the user's device, as a stand-alone software package, partly on the user's computing device and partly on a remote computing device or entirely on the remote computing device or server.

[0190] In addition, embodiments of the present application can also be a computer readable storage medium having stored thereon computer program instructions which, when executed by a processor, cause the processor to perform steps of the methods according to various embodiments of the present application described in the above "Exemplary Methods" section of the specification.

[0191] The computer readable storage medium can be any combination of one or more non-transitory media. The non-transitory medium can be a non-transitory signal medium or a non-transitory storage medium. The non-transitory storage medium can include, but is not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, or device, or any suitable combination of the above. More specific examples (a non-exhaustive list) of the non-transitory storage medium include the following: an electrical connection having one or more wires, a portable disc, a hard disk, a random access memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or flash memory), an optical fiber, a portable compact disc read-only memory (CD-ROM), an optical storage device, a magnetic storage device, or any suitable combination of the above.

[0192] The above describes the basic principles of the present application in conjunction with specific embodiments, but it should be noted that the advantages, benefits, effects and the like mentioned in the present application are only examples and are not limiting, and these advantages, benefits, effects and the like cannot be considered as necessary for each embodiment of the present application. In addition, the above specific details disclosed are only for the purpose of example and understanding, and are not limiting, and the above details do not limit the present application to be necessarily implemented with the above specific details.

[0193] Each embodiment in the specification is described in a progressive manner, and each embodiment focuses on the difference from other embodiments, and the same or similar parts between each embodiment can be understood by referring to each other. For the system embodiment, since it basically corresponds to the method embodiment, the description is relatively simple, and the relevant parts can be understood by referring to the part of the method embodiment.

[0194] The block diagrams of the devices, systems, apparatuses, systems involved in the present application are only illustrative examples and are not intended to require or imply the connection, arrangement, configuration shown in the block diagram. As those skilled in the art will recognize, these devices, systems, apparatuses, systems can be connected, arranged, configured in any manner. Words such as "include", "contain", "have" and the like are open-ended words, which mean "including but not limited to", and can be used interchangeably. The words "or" and "and" used herein mean the word "and / or", and can be used interchangeably unless the context clearly indicates otherwise. The word "such as" used herein means the phrase "such as but not limited to", and can be used interchangeably.

[0195] The method and system of the present application can be implemented in many ways. For example, the method and system of the present application can be implemented by software, hardware, firmware or any combination of software, hardware and firmware. The above order of steps for the method is only for illustration, and the steps of the method of the present application are not limited to the above specific description, unless otherwise specifically described. In addition, in some embodiments, the present application can also be implemented as programs recorded in recording media, which include machine-readable instructions for implementing the method according to the present application. Therefore, the present application also covers the recording media storing the programs for executing the method according to the present application.

[0196] It is also important to note that the systems, devices and methods of the present application can be embodied in a variety of forms without departing from the spirit of the application. Furthermore, the foregoing description has been directed to certain embodiments of the application. It is recognized that modifications, additions and / or omissions can be made to these embodiments without departing from the spirit of the application. Accordingly, the particular arrangements disclosed are meant to be illustrative only and not limiting as to the scope of the application. It is thus intended that the true scope of the application be indicated by the appended claims together with their full scope of equivalents.

[0197] The foregoing description has been presented for purposes of illustration and description. Furthermore, the description is not intended to limit the embodiments of the application to the forms disclosed herein. Although the examples and embodiments have been discussed with reference to particular aspects, those skilled in the art will readily recognize that the examples and embodiments are merely illustrative of the principles and applications of the present application. Numerous modifications, adaptations, changes, additions, and omissions can be made to the examples and embodiments without departing from the spirit and scope of the application.

Claims

1. A method for remote calibration of measuring equipment, characterized in that, include: The loss index is calculated based on the current characteristics of the current signal extracted during the monitoring period, and the phase offset of each harmonic is determined based on the loss index. An environmental gain coefficient is constructed based on the ambient temperature and humidity during the environmental management cycle. Based on the fundamental amplitude of the current signal during the monitoring period and the environmental gain coefficient, a current correction coefficient is constructed. The amplitude of each harmonic in the next monitoring cycle is corrected according to the current correction coefficient, and the phase of each harmonic in the next monitoring cycle is corrected according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

2. The method according to claim 1, characterized in that, The loss index is calculated based on the current characteristics of the extracted current signal within the monitoring period, including: Acquire current signals during the detection period; The amplitude values ​​of each harmonic of the current signal are extracted using the Fast Fourier Transform method; Calculate the magnetic flux intensity based on the amplitude of each harmonic and the proportional coefficient of the transformer. The loss index is calculated based on the magnetic induction intensity.

3. The method according to claim 2, characterized in that, The expression for calculating the loss index is as follows: In the formula, P is the loss exponent, K1 is the hysteresis loss coefficient, K2 is the eddy current loss coefficient, fn is the frequency exponent, fn=n×50Hz; Bn is the magnetic induction intensity of the nth harmonic.

4. The method according to claim 1, characterized in that, The phase shift of each harmonic is determined based on the loss exponent, including: Extract the effective voltage value of the nth harmonic of the current signal; The equivalent resistance of the nth harmonic is calculated based on the effective voltage value and the loss exponent. Calculate the phase offset of the nth harmonic using the equivalent resistance, magnetizing inductance of the current transformer, and frequency index.

5. The method according to claim 4, characterized in that, The formula for calculating the equivalent resistance is: Rn=Vn 2 / P In the formula, Vn is the effective value of voltage; P is the loss exponent; The expression for calculating the phase offset θn is: θn=arctan(2×π×fn×L / Rn) In the formula, θn is the nth harmonic offset; fn is the frequency exponent; and L is the magnetizing inductance of the transformer.

6. The method according to claim 1, characterized in that, Based on the ambient temperature and humidity during the monitoring period, an environmental gain coefficient is constructed, including: Calculate the ambient temperature threshold based on the ambient temperature and the ambient humidity; The water vapor state is determined based on the ambient temperature threshold and the ambient humidity, and the environmental gain coefficient is constructed based on the water vapor state.

7. The method according to claim 6, characterized in that, The calculation expression for the ambient temperature threshold is as follows: In the formula, Y is the ambient temperature threshold, β1 is the temperature offset coefficient, β2 is the temperature empirical constant; t is the ambient temperature, and s is the ambient humidity.

8. The method according to claim 7, characterized in that, The water vapor state is determined based on the ambient temperature threshold and the ambient humidity, and the environmental gain coefficient is constructed based on the water vapor state, including: If the ambient temperature is less than or equal to T+2 and the ambient humidity is greater than or equal to a preset humidity threshold s1, the water vapor state is determined to be an abnormal state, and an environmental gain coefficient of [1+γ×(s-s1)] is constructed, where γ is an adjustment factor; otherwise, the water vapor state is determined to be a normal state, and an environmental gain coefficient of 1 is constructed.

9. The method according to claim 1, characterized in that, Also includes: The environmental gain coefficient is updated based on the change in the protection ring capacitance during the environmental management cycle.

10. The method according to claim 9, characterized in that, The environmental gain coefficient is updated based on the change in the protection ring capacitance during the environmental management cycle, including: The rate of change of the protective ring capacitance BH is calculated based on the protective ring capacitance D1 collected in the environmental management cycle and the protective ring capacitance D2 collected in the previous environmental management cycle, where Δt is the duration of the environmental management cycle. If the change rate BH of the protective ring capacitance is greater than the preset change rate threshold b0, then the environmental gain coefficient is updated to {HK×1+η×ln[5×(BH-b0) / (BH+b0)+1] / ln6}, where η is the update coefficient and HK is the environmental gain coefficient before the update; otherwise, the environmental gain coefficient is not updated.

11. The method according to claim 1, characterized in that, Based on the fundamental amplitude of the current signal within the monitoring period and the environmental gain coefficient, a current correction coefficient is constructed, including: The current correction weighting factor is determined based on the fundamental amplitude of the current signal within the monitoring period. The current correction coefficient is constructed based on the current correction weight shadow and the environmental gain coefficient.

12. The method according to claim 11, characterized in that, The expression for the current correction weighting factor is: In the formula, W is the current correction weighting factor, F1 is the fundamental amplitude during the monitoring period, and Fn is the amplitude of the nth harmonic.

13. The method according to claim 11, characterized in that, The current correction coefficient is constructed based on the current correction weight shadow and the environmental gain coefficient, including: When the current correction weight factor is less than or equal to the compensation threshold r0, the current correction coefficient is constructed as [z1×(1-0.1×W)×environmental gain coefficient], otherwise the current correction coefficient is constructed as [z2×(1-0.1×W)×environmental gain coefficient], where z1 is the first compensation factor and z2 is the second compensation factor.

14. The method according to claim 1, characterized in that, The amplitude of each harmonic of the calibration current is Fnjj = Fnj × current correction coefficient, where Fnj is the measured value of the nth harmonic amplitude in the next monitoring cycle. The harmonic phases of the calibration current θn is the measured value of the nth harmonic phase in the next monitoring cycle; θn is the nth harmonic offset.

15. A remote calibration device for metrological equipment, characterized in that, include: The calculation module is used to calculate the loss index based on the current characteristics of the current signal extracted within the monitoring period, and to determine the phase offset of each harmonic based on the loss index. The first construction module is used to construct the environmental gain coefficient based on the ambient temperature and humidity during the environmental management cycle. The second construction module is used to construct a current correction coefficient based on the fundamental amplitude of the current signal during the monitoring period and the environmental gain coefficient. The calibration module is used to correct the amplitude of each harmonic in the next monitoring cycle according to the current correction coefficient, and to correct the phase of each harmonic in the next monitoring cycle according to the phase offset of each harmonic, so as to obtain the calibration current for the next monitoring cycle.

16. The apparatus according to claim 15, characterized in that, The calculation module calculates the loss index based on the current characteristics of the extracted current signal within the monitoring period, including: The acquisition submodule is used to acquire the current signal during the detection period; The extraction submodule is used to extract the amplitude values ​​of each harmonic of the current signal using the fast Fourier transform method; The first calculation submodule is used to calculate the magnetic induction intensity based on the amplitude of each harmonic and the proportional coefficient of the transformer. The second calculation submodule is used to calculate the loss index based on the magnetic induction intensity.

17. A computer-readable storage medium, characterized in that, The storage medium stores a computer program for performing the method described in any one of claims 1-14.

18. An electronic device, characterized in that, The electronic device includes: processor; Memory used to store the processor's executable instructions; The processor is configured to read the executable instructions from the memory and execute the instructions to implement the method described in any one of claims 1-14.

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