Reflective array antenna control method and system based on broadband dual-polarization unit

Abstract

The invention discloses a reflective array antenna control method and system based on a broadband dual-polarization unit, and the method comprises the steps: obtaining a target wave beam pointing instruction, and carrying out the orthogonal decomposition of the target wave beam pointing instruction into a first polarization control vector and a second polarization control vector; calculating a theoretical phase frequency spectrum of each unit according to the polarization control vector; calling a preset database to extract a basic phase spectrum; quantitative mapping is carried out by calculating a matching error between a theory and a basic phase frequency spectrum, a phase control code containing the first polarization and the second polarization is obtained and loaded to a corresponding broadband dual-polarization unit to drive the switching of a physical state of the broadband dual-polarization unit, and real-time reconstruction of a wave beam is realized. Compared with the prior art, the antenna can overcome the defects that a traditional reflective array antenna is serious in polarization component coupling, low in phase matching degree in a broadband range and inaccurate in phase control code acquisition, and remarkably enhances the independent pointing precision and the full-band gain stability of dual-polarization beams. Therefore, flexible reconstruction of the wave beam in polarization and frequency dimensions is realized.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of antenna technology and microwave engineering, and more particularly, to a reflection array antenna control method and system based on a wideband dual-polarized unit. BACKGROUND

[0002] With the evolution of the fifth generation and future wireless communication systems to higher frequency bands, larger capacity and more complex application scenarios, unprecedented high standards are required for the beam steering flexibility, spectrum utilization efficiency and multi-polarization information carrying capacity of the antenna system. The phase switching speed, operating bandwidth, polarization freedom and integration of the unit of the reconfigurable metasurface unit, which is the core device for realizing intelligent electromagnetic environment regulation, directly determines the performance upper limit of the entire communication system in complex scenarios such as dynamic measurement and control and perception integration. Among them, the reflection array antenna is attracting attention because it combines the high gain of the traditional parabolic antenna and the flexible beam scanning capability of the phased array antenna; the reconfigurable reflective metasurface with 1-bit phase quantization becomes an ideal solution for realizing low-cost and high-agility beam scanning because of its simple control and low loss.

[0003] In the prior art, although active reflection arrays are improved by integrating active devices and reflection array structures to realize efficient and flexible electromagnetic scattering control, there are still problems of serious polarization component coupling, low phase matching degree in a wideband range, and inaccurate phase control code acquisition.

[0004] Therefore, how to provide a reflection array antenna control method based on a wideband dual-polarized unit, which can overcome the shortcomings of traditional reflection array antennas, such as serious polarization component coupling, low phase matching degree in a wideband range, and inaccurate phase control code acquisition, has become a technical problem that needs to be solved by those skilled in the art. SUMMARY

[0005] To solve the above technical problems, the present application provides a reflection array antenna control method based on a wideband dual-polarized unit, which can overcome the shortcomings of traditional reflection array antennas, such as serious polarization component coupling, low phase matching degree in a wideband range, and inaccurate phase control code acquisition, and significantly enhance the independent pointing accuracy of dual-polarized beams and the stability of full-band gain, thereby realizing flexible reconstruction of beams in the polarization and frequency dimensions.

[0006] The first technical solution provided by the present application is as follows: The application provides a wideband dual-polarized unit-based reflectarray control method, including the following steps: S1, obtaining a target beam pointing instruction and decomposing the target beam pointing instruction into a first polarization control vector and a second polarization control vector, the first polarization control vector and the second polarization control vector being orthogonal to each other; S2, calculating a theoretical phase spectrum of each wideband dual-polarized unit according to the first polarization control vector and the second polarization control vector; S3, extracting a basic phase spectrum of the wideband dual-polarized unit according to a preset wideband frequency response database; S4, calculating a matching error between the theoretical phase spectrum and the basic phase spectrum of each wideband dual-polarized unit, and quantitatively mapping the theoretical phase spectrum based on the matching error to obtain a phase control code, the phase control code including a first polarization phase control code and a second polarization phase control code; wherein the wideband dual-polarized unit has two groups of orthogonally arranged dipole groups, the physical working state of the dipole group including a first conduction state and a second cutoff state; and the phase control code is used to drive the physical working state of the dipole group to switch to a physical working state corresponding to the phase control code.

[0007] Further, in a preferred mode of the application, the step of calculating the matching error between the theoretical phase spectrum and the basic phase spectrum of each wideband dual-polarized unit includes: obtaining a working frequency range of the wideband dual-polarized unit, discretely processing the working frequency range, and obtaining a plurality of frequency sampling points; respectively obtaining a theoretical compensation phase and a physical phase response of each frequency sampling point, and calculating an original phase difference between the theoretical compensation phase and the physical phase response at each frequency sampling point; based on each frequency sampling point, weighting the absolute value of the original phase difference to obtain a weighted phase error component; adding up the weighted phase error components corresponding to each frequency sampling point to obtain a matching error.

[0008] Further, in a preferred mode of the application, the step of weighting the absolute value of the original phase difference includes: obtaining a center frequency of the working frequency range and calculating a frequency deviation absolute value of each frequency sampling point from the center frequency value; mapping the frequency deviation absolute value according to a preset attenuation function to obtain a frequency weighting coefficient corresponding to each frequency sampling point; multiplying the absolute value of the original phase difference by the corresponding frequency weighting coefficient to obtain the weighted phase error component.

[0009] Further, in a preferred manner of the present application, the step of constructing the attenuation function comprises: calling the wideband frequency response database, extracting simulation gain data of the wideband dual-polarized unit in the working frequency band, and constructing a gain frequency characteristic curve according to the simulation gain data; extracting a maximum gain value of the gain frequency characteristic curve at the center frequency, and performing normalization processing on the gain frequency characteristic curve according to the maximum gain value to obtain a normalized gain distribution; performing function fitting on the normalized gain distribution to obtain an attenuation function.

[0010] Further, in a preferred manner of the present application, the step of quantitatively mapping the theoretical phase spectrum based on the matching error to obtain a phase control code comprises: obtaining a first basic phase spectrum of a first on state and a second basic phase spectrum of a second off state according to the wideband frequency response database; calculating a first matching error of the theoretical phase spectrum and the first basic phase spectrum, and a second matching error of the theoretical phase spectrum and the second basic phase spectrum, respectively; comparing the first matching error and the second matching error, if the first matching error is less than the second matching error, the control code of the first basic phase spectrum is determined as the phase control code; if the first matching error is greater than the second matching error, the control code of the second basic phase spectrum is determined as the phase control code.

[0011] Further, in a preferred manner of the present application, the step of calculating the theoretical phase spectrum of each wideband dual-polarized unit comprises: establishing a spatial coordinate system of the metasurface antenna, and obtaining spatial position coordinates of each wideband dual-polarized unit in the spatial coordinate system; determining a wave vector of the target beam according to the target beam pointing instruction, and calculating a spatial wave path difference between the wave vector and each spatial position coordinate; converting the spatial wave path difference into a phase delay based on frequency sampling points, and combining the phase delay of each frequency sampling point to generate a theoretical phase spectrum.

[0012] Further, in a preferred manner of the present application, the step of decomposing the target beam pointing instruction into a first polarization control vector and a second polarization control vector comprises: obtaining a first polarization direction corresponding to a first polarization port of the wideband dual-polarized unit, and a second polarization direction corresponding to a second polarization port; Orthogonal project the target beam pointing instruction corresponding to the target electric field vector to the first polarization direction and the second polarization direction respectively, and obtain a first polarization control vector projected on the first polarization direction and a second polarization control vector projected on the second polarization direction.

[0013] Further, in a preferred mode of the present application, the wideband dual-polarized unit is configured into a first on-state and a second off-state respectively, and a first phase control code corresponding to the first on-state and a second phase control code corresponding to the second off-state are established. Electromagnetic simulation is performed on the wideband dual-polarized unit to obtain basic phase spectrum and simulation gain data of the wideband dual-polarized unit in the first on-state and basic phase spectrum and simulation gain data of the wideband dual-polarized unit in the second off-state respectively. A mapping index relationship between the basic phase spectrum, the simulation gain data and the phase control code is established, and a wideband frequency response database is constructed based on the mapping index relationship.

[0014] The present application provides a second technical solution as follows: The present application also provides a wideband dual-polarized unit-based reflectarray antenna control system, which is used to execute the wideband dual-polarized unit-based reflectarray antenna control method described above, and comprises: An array antenna surface composed of a plurality of wideband dual-polarized units arranged periodically; A control module electrically connected to each wideband dual-polarized unit in the array antenna surface, used to execute the wideband dual-polarized unit-based reflectarray antenna control method.

[0015] Further, in a preferred mode of the present application, the wideband dual-polarized unit comprises: A dielectric layer comprising a top dielectric layer, a middle dielectric layer and a bottom dielectric layer arranged in sequence; The top end of the top dielectric layer is provided with a radiation layer, and the radiation layer comprises a dipole group, a ground patch and a switch assembly; The number of the dipole group is 2 groups, and two dipoles in the same group are arranged oppositely, and four dipoles of two dipole groups are arranged orthogonally; The ground patch is arranged between the two dipoles of the dipole group and connected to the dipoles through the switch assembly; A ground metal layer is arranged between the top dielectric layer and the middle dielectric layer, a choke metal layer is arranged between the middle dielectric layer and the bottom dielectric layer, and a bias metal layer is arranged on the lower surface of the bottom dielectric layer; The ground patch is connected with the ground metal layer through the top layer dielectric layer. The dipole passes through the ground metal layer through a metalized via and is insulated from the ground metal layer, and the dipole is electrically connected downward to the choke metal layer and the bias metal layer.

[0016] The application provides a kind of based on wideband dual polarization unit's reflection array antenna control method, it can overcome the shortcomings of traditional reflection array antenna polarization component coupling serious, low in wideband range phase matching degree and not accurate phase control code acquisition, significantly enhance the independent pointing accuracy of dual polarized beam and full-band gain stability, to realize the flexible reconstruction of beam in polarization and frequency dimension.The kind of based on wideband dual polarization unit's reflection array antenna method includes: S1 obtains target beam pointing instruction, and the target beam pointing instruction is decomposed into first polarization control vector and second polarization control vector, the first polarization control vector and second polarization control vector are orthogonal to each other;S2 according to the first polarization control vector and the second polarization control vector, calculate the theoretical phase spectrum of each wideband dual polarization unit;S3 according to the preset wideband frequency response database, extract the basic phase spectrum of the wideband dual polarization unit;S4 calculate the matching error between the theoretical phase spectrum of each wideband dual polarization unit and the basic phase spectrum, and the theoretical phase spectrum is quantized mapping based on the matching error, obtain phase control code, the phase control code includes first polarization phase control code and second polarization phase control code;Wherein, the wideband dual polarization unit has 2 groups of orthogonal setting dipole group, the physical working state of the dipole group includes first conduction state and second cut-off state;The phase control code is used to drive the physical working state of the dipole group to switch to the physical working state corresponding to the phase control code.Wherein, by acquiring the target beam pointing instruction and decomposing the target beam pointing instruction into mutually orthogonal first polarization control vector and second polarization control vector, the vector orthogonal decomposition mechanism breaks the logical barrier of mutual restraint of components in the prior art of dual-polarized beam regulation, establishes an independent decoupling framework of polarization dimension, and effectively solves the problem of serious polarization component coupling in the traditional reflective array antenna beam regulation process. Secondly, by calculating the theoretical phase spectrum of each wideband dual-polarized unit according to the polarization control vector, and combining the preset database to extract the basic phase spectrum, a global comparison system of full-band spectrum and basic response is constructed at the frequency domain layer, which provides a continuous observation window for the phase consistency in the wideband range, prevents the performance deterioration at the edge of the frequency band caused by relying only on single-frequency point phase design, and significantly enhances the phase matching degree in the wideband range. The mechanism of utilizing the matching error between the calculated theoretical phase spectrum and the basic phase spectrum and quantitatively mapping based on the matching error realizes the accurate alignment of the theoretical beam requirement and the physical unit state, ensures that the finally obtained phase control code can drive the wideband dual-polarized unit to switch to the physical working state with the minimum error, avoids the mapping distortion caused by the lack of error optimization in the traditional scheme, and greatly improves the accuracy of the phase control code acquisition. Compared with the prior art, the present application can overcome the shortcomings of serious polarization component coupling of traditional reflective array antenna, low phase matching degree in the wideband range and inaccurate phase control code acquisition, significantly enhance the independent pointing accuracy of dual-polarized beam and the stability of full-band gain, and realize the flexible reconstruction of beam in polarization and frequency dimensions. BRIEF DESCRIPTION OF DRAWINGS

[0017] In order to more clearly illustrate the technical solutions in the embodiments of the present application or the prior art, the drawings needed to be used in the embodiments or the prior art description will be briefly introduced. Obviously, the drawings in the following description are only some embodiments of the present application, and other drawings can be obtained by those skilled in the art without creative labor.

[0018] Figure 1 The step flow chart of the reflective array antenna control method based on wideband dual-polarized unit provided by the embodiments of the present application; Figure 2 The normalized directional diagram of X polarization scanning azimuth plane at a working frequency of 8.5GHz; Figure 3 The normalized directional diagram of X polarization scanning azimuth plane at a working frequency of 10.5GHz; Figure 4 The normalized directional diagram of X polarization scanning azimuth plane at a working frequency of 12.5GHz; Figure 5 The normalized directional diagram of Y polarization scanning azimuth plane at a working frequency of 8.5GHz; Figure 6 The normalized azimuth pattern of the Y-polarized scanning plane at an operating frequency of 10.5 GHz; Figure 7 The normalized azimuth pattern of the Y-polarized scan at an operating frequency of 12.5 GHz; Figure 8 The following is a diagram showing the reflection amplitude and phase curves of a broadband dual-polarization unit provided in an embodiment of the present invention; Figure 9 This is a diagram showing the dipole current distribution in the first conduction state. Figure 10 This is a diagram showing the current distribution of the grounding metal layer under the first conduction state. Figure 11 This is a diagram showing the dipole current distribution under the second cutoff state. Figure 12 This is a diagram showing the current distribution of the grounding metal layer under the second cutoff state. Figure 13 A three-dimensional structural diagram of a broadband dual-polarization unit; Figure 14 This is a hierarchical diagram of a broadband dual-polarization unit; Figure 15 This is a schematic diagram of the radiative layer of a broadband dual-polarization unit. Figure 16 A three-dimensional perspective view of the metallized vias of a broadband dual-polarization cell; Figure 17 This is a cross-sectional view of a broadband dual-polarization unit.

[0019] Reference numerals: 1. Dielectric layer; 101. Top dielectric layer; 102. Middle dielectric layer; 103. Bottom dielectric layer; 2. Radiation layer; 201. Dipole group; 201a. Dipole; 202. Grounding patch; 203. Switching assembly; 3. Metal layer; 301. Grounding metal layer; 302. Choke metal layer; 303. Bias metal layer; 4. Metallized via. Detailed Implementation

[0020] To enable those skilled in the art to better understand the technical solutions of this invention, the technical solutions of the embodiments of this invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only a part of the embodiments of this invention, and not all of them. Based on the embodiments of this invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of this invention.

[0021] It should be noted that when a component is referred to as being "fixed to" or "set on" another component, it can be directly on or indirectly set on the other component; when a component is referred to as being "connected to" another component, it can be directly connected to or indirectly connected to the other component.

[0022] It should be understood that the terms "length", "width", "upper", "lower", "front", "rear", "first", "second", "vertical", "horizontal", "top", "bottom", "inner", "outer", etc., indicate the orientation or positional relationship based on the orientation or positional relationship shown in the accompanying drawings. They are only for the convenience of describing the present invention and simplifying the description, and do not indicate or imply that the device or element referred to must have a specific orientation, or be constructed and operated in a specific orientation. Therefore, they should not be construed as limitations on the present invention.

[0023] Furthermore, the terms "first" and "second" are used for descriptive purposes only and should not be construed as indicating or implying relative importance or implicitly specifying the number of indicated technical features. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more of that feature. In the description of this invention, "a plurality of" or "several" means two or more, unless otherwise explicitly specified.

[0024] It should be noted that the structures, proportions, sizes, etc., shown in the accompanying drawings of this specification are only for the purpose of assisting those skilled in the art in understanding and reading the content disclosed in the specification, and are not intended to limit the conditions under which the present invention can be implemented. Therefore, they have no substantial technical significance. Any modifications to the structure, changes in the proportions, or adjustments to the size, without affecting the effects and objectives that the present invention can produce, should still fall within the scope of the technical content disclosed in the present invention.

[0025] like Figures 1 to 8 As shown, the reflective array antenna control method based on broadband dual-polarization unit provided by the embodiments of the present invention can overcome the shortcomings of traditional reflective array antennas, such as severe polarization component coupling, low phase matching degree in the broadband range, and inaccurate phase control code acquisition. It significantly enhances the independent pointing accuracy and full-band gain stability of the dual-polarization beam, thereby realizing flexible beam reconstruction in the polarization and frequency dimensions.

[0026] A control method for a reflective array antenna based on a broadband dual-polarization unit includes the following steps: S1 acquiring a target beam pointing command and decomposing the target beam pointing command into a first polarization control vector and a second polarization control vector, the first polarization control vector and the second polarization control vector being orthogonal to each other; S2 calculating the theoretical phase spectrum of each broadband dual-polarization unit based on the first polarization control vector and the second polarization control vector; S3 extracting the fundamental phase spectrum of the broadband dual-polarization unit based on a preset broadband frequency response database; S4 calculating the matching error between the theoretical phase spectrum and the fundamental phase spectrum of each broadband dual-polarization unit, and quantizing and mapping the theoretical phase spectrum based on the matching error to obtain a phase control code, the phase control code including a first polarization phase control code and a second polarization phase control code; wherein, the broadband dual-polarization unit has two sets of orthogonally arranged dipole groups, the physical operating states of the dipole groups including a first conduction state and a second cutoff state; the phase control code is used to drive the physical operating state of the dipole groups to switch to the physical operating state corresponding to the phase control code. Specifically, by acquiring the target beam pointing command and decomposing it into two mutually orthogonal polarization control vectors (first and second), this vector orthogonal decomposition mechanism breaks through the logical barrier of mutual constraint between components in existing dual-polarization beam control technologies. It establishes an independent decoupling framework for the polarization dimension, effectively solving the problem of severe polarization component coupling during beam control of traditional reflector array antennas. Secondly, by calculating the theoretical phase spectrum of each broadband dual-polarization unit based on the polarization control vector and extracting the fundamental phase spectrum from a pre-set database, a global comparison system between the full-band spectrum and the fundamental response is constructed in the frequency domain. This provides a continuous observation window for phase consistency across the broadband range, preventing performance degradation at the bandwidth edges due to reliance on single-frequency phase design and significantly enhancing the system's performance. The invention achieves precise alignment between theoretical beam requirements and physical unit states by utilizing a mechanism that calculates the matching error between the theoretical phase spectrum and the fundamental phase spectrum and performs quantization mapping based on the matching error. This ensures that the final acquired phase control code can drive the broadband dual-polarization unit to switch to the physical operating state with minimal error, avoiding mapping distortion caused by the lack of error optimization in traditional schemes, thereby significantly improving the accuracy of phase control code acquisition. Compared with existing technologies, this invention overcomes the shortcomings of traditional reflective array antennas, such as severe polarization component coupling, low phase matching within the broadband range, and inaccurate phase control code acquisition. It significantly enhances the independent pointing accuracy and full-band gain stability of the dual-polarization beam, thereby achieving flexible beam reconstruction in the polarization and frequency dimensions.

[0027] The following describes in detail the steps of the control method for a reflective array antenna based on a broadband dual-polarization unit, using specific embodiments.

[0028] Specifically, in a specific embodiment of the present invention, the step of calculating the matching error between the theoretical phase spectrum and the fundamental phase spectrum of each broadband dual-polarization unit includes: obtaining the operating frequency band of the broadband dual-polarization unit; discretizing the operating frequency band to obtain several frequency sampling points; obtaining the theoretical compensation phase and physical phase response of each frequency sampling point, and calculating the original phase difference between the theoretical compensation phase and the physical phase response of each frequency sampling point; weighting the absolute value of the original phase difference based on each frequency sampling point to obtain a weighted phase error component; and summing the weighted phase error components corresponding to each frequency sampling point to obtain the matching error.

[0029] In a specific embodiment of the present invention, the preset operating frequency band of the broadband dual-polarization unit in the actual application scenario is first obtained. For example, a specific range of the X-band is selected as the target interval, and the continuous operating frequency band is discretized. The frequency band is divided into multiple equally spaced frequency sampling points according to the preset frequency step size, or several key frequency points are selected as frequency sampling points according to the channel division standard of the communication protocol. Then, for each frequency sampling point, the theoretical compensation phase corresponding to the frequency point is parsed from the beam control command, and the physical phase response value of the broadband dual-polarization unit at that frequency point is retrieved from the pre-established database. The theoretical compensation phase refers to the ideal phase delay value required to compensate for the spatial path difference caused by the broadband dual-polarization unit being located in a specific spatial position of the array, thereby ensuring that the electromagnetic waves reflected by units at different positions are superimposed in phase in the direction of the preset target beam. The original phase difference at each frequency sampling point is calculated by subtracting the physical phase response value from the theoretical compensation phase. Then, based on the importance of each frequency sampling point within the antenna's operating bandwidth, the absolute value of the calculated original phase difference is weighted, i.e., a corresponding weight coefficient is assigned to each frequency sampling point. The absolute value of the original phase difference is multiplied by this weight coefficient to obtain the weighted phase error component corresponding to that frequency point. The setting of this weight coefficient can focus on maintaining the performance of the center frequency or high-gain frequency. Finally, the weighted phase error components corresponding to all frequency sampling points are summed to obtain a comprehensive matching error value that characterizes the phase matching degree of the entire frequency band. The smaller the matching error value, the higher the fit between the current physical state and the theoretical beam requirement in the entire broadband range. It can effectively take into account the phase consistency between the frequency band edge and the center frequency and avoid the frequency band distortion problem caused by single-frequency point matching.

[0030] like Figures 2 to 7As shown, to verify the effectiveness of the above-mentioned broadband error calculation scheme in improving the broadband performance of reflector array antennas, a test environment based on full-wave electromagnetic simulation software was built, and a broadband dual-polarization unit with an operating frequency band of 8.8 GHz to 12.1 GHz was selected as the test object. The experiment first obtained the basic phase data of the unit according to the method of this invention. This unit achieved a stable 180-degree phase difference within a range covering 31.6% of the relative bandwidth, providing a physical basis for broadband error matching. Subsequently, the experimental group used the broadband weighted error calculation method proposed in this invention for phase optimization, and selected typical frequencies covering the low frequency of 8.5 GHz, the center frequency of 10.5 GHz, and the high frequency of 12.5 GHz in the simulation environment. The sampling points were used for verification. Under the same main beam pointing command, thanks to the summation and weighted control of the frequency sampling point errors, the antenna maintained a high degree of consistency in the main beam pointing at three frequency points with a large range of 8.5GHz, 10.5GHz, and 12.5GHz. The beam divergence or pointing deflection caused by frequency shift, which is common in traditional single-frequency design, did not occur. The experimental results show that the sidelobe electrical average of the beam at the three frequency points in the attached figure of the specification is less than -10dB and the main lobe shape is full. This fully proves that the matching error calculation mechanism based on the summation of frequency sampling points can effectively suppress the frequency dispersion effect and significantly improve the beam pointing accuracy and gain stability of the reflector array antenna under broadband operating conditions.

[0031] Specifically, in a specific embodiment of the present invention, the step of weighting the absolute value of the original phase difference includes: obtaining the center frequency of the working frequency band and calculating the absolute value of the frequency deviation between each frequency sampling point and the center frequency value; mapping the absolute value of the frequency deviation according to a preset attenuation function to obtain the frequency weighting coefficient corresponding to each frequency sampling point; and multiplying the absolute value of the original phase difference with the corresponding frequency weighting coefficient to obtain the weighted phase error component.

[0032] In this embodiment of the invention, the first step is to accurately locate the spectral centroid of the operating frequency band. Typically, the arithmetic mean of the operating frequency band is selected as the center frequency reference. For example, in the Ka band, within the range of 26 GHz to 30 GHz, 28 GHz is set as the center frequency. Then, each discretized frequency sampling point is traversed, and the difference between the current frequency sampling point and the center frequency is calculated by numerical subtraction. The absolute value of this difference is then taken to obtain the absolute value of the frequency deviation, which directly reflects the degree to which the current sampling point deviates from the center operating frequency. Next, based on a pre-defined attenuation function model, such as using a Gaussian distribution function or a cosine square roll-off function as the mapping kernel, the calculated absolute value of the frequency deviation is input as the independent variable into the function model. Since the attenuation function has… The characteristic of a maximum weight at the center and decreasing weights at the edges allows for the calculation of a frequency weighting coefficient corresponding to each frequency sampling point. This results in sampling points near the center frequency receiving a high weight close to 1, while sampling points at the edge of the frequency band receive a lower weight. Finally, a weighting operation is performed, multiplying the absolute value of the original phase difference at each frequency sampling point by the corresponding frequency weighting coefficient to obtain the weighted phase error component. The magnitude of this component depends not only on the difference between the physical phase and the theoretical phase, but also on the importance of that frequency point in the entire operating bandwidth. This ensures that during subsequent error accumulation, the optimization algorithm prioritizes the phase matching accuracy of the center frequency band and the high-efficiency frequency band, preventing gain collapse in the core operating frequency band of the antenna due to excessive accommodation of phase errors at edge frequencies.

[0033] Specifically, in a specific embodiment of the present invention, the steps for constructing the attenuation function include: calling a broadband frequency response database, extracting the simulated gain data of the broadband dual-polarization unit in the operating frequency band, and constructing a gain frequency response curve based on the simulated gain data; extracting the maximum gain value of the gain frequency response curve at the center frequency, and normalizing the gain frequency response curve based on the maximum gain value to obtain a normalized gain distribution; and performing function fitting on the normalized gain distribution to obtain the attenuation function.

[0034] In an embodiment of the present invention, a pre-set broadband frequency response database is first invoked. This database is established using full-wave electromagnetic simulation software based on the finite element method or finite integral method. In the simulation settings, periodic boundary conditions are applied to the X-axis and Y-axis boundaries of the broadband dual-polarization unit to simulate an infinite array environment. A Floquet port is set in the Z-axis direction for broadband plane wave excitation, thereby obtaining discrete gain data points in the range of 8.8 GHz to 12.1 GHz with a step size of 0.1 GHz. Subsequently, to eliminate the data discontinuity caused by the frequency sampling interval, a cubic spline interpolation algorithm is used to smooth the discrete gain data, thereby generating a smooth gain frequency response curve with continuously changing curvature across the entire frequency band. Next, using the center frequency of 10.5 GHz as a reference, the maximum gain value on the curve is extracted as the normalization denominator. The gain values ​​of all frequency points on the curve are divided by this maximum gain value to obtain a normalized gain data set with values ​​distributed between 0 and 1. Finally, a frequency-based... A Gaussian decay function model with frequency deviation as the independent variable is mathematically represented as an exponential function with the natural constant as the base. The exponent is the negative of the ratio of the square of the frequency deviation to the decay coefficient. The decay coefficient in this model is iteratively solved using the nonlinear least squares method. The specific process is as follows: First, an estimated decay coefficient is initialized. The sum of squared residuals between the current model output value and the actual normalized gain data is calculated. Then, the gradient direction of the sum of squared residuals with respect to the decay coefficient is calculated, and the decay coefficient is updated along the gradient descent direction with a preset learning rate. The above steps of calculating residuals, solving gradients, and updating parameters are repeated until the change in the sum of squared residuals calculated in two adjacent iterations is less than a preset convergence threshold. For example, the convergence threshold can be set to 10 to the power of -6. At this point, the corresponding decay coefficient is the optimal solution, thus determining the final decay function expression. This process transforms discrete physical simulation data into a continuous and analytical mathematical expression, providing a differentiable and accurate error weight model for subsequent control algorithms.

[0035] To verify the accuracy of the attenuation function constructed based on cubic spline interpolation and nonlinear fitting, and its impact on beam quality, a 16×16 element reflector array antenna numerical simulation platform was built, and tests were conducted in the 8.8GHz to 12.1GHz frequency band. Two control groups were set up in the experiment. The experimental group used the fitting method detailed in this embodiment, i.e., first obtaining a continuous curve through cubic spline interpolation, and then iteratively calculating the optimal Gaussian attenuation constant using the least squares method. The control group used the traditional linear interpolation method to directly call discrete data, or used an unoptimized standard cosine function as a fixed-weight attenuation model. Comparative data showed that at 12.0GHz, far from the center frequency, the control group, due to the use of an unoptimized standard function, had a lower attenuation rate. The deviation between the weighting coefficients and the decay characteristics of the actual physical gain of the unit resulted in a prediction error of approximately 2.1 dB for the main lobe gain and an increase in the sidelobe level to -13 dB. However, the experimental group benefited from the preservation of frequency response details by cubic spline interpolation and the precise locking of attenuation parameters by the least squares method. The correlation coefficient between the generated function curve and the actual physical test curve exceeded 0.99, reducing the beam gain prediction error at 12.0 GHz to within 0.3 dB and effectively suppressing the sidelobe level to below -17 dB. This result strongly demonstrates the necessity of transforming physical data into a mathematical model through high-order interpolation and nonlinear fitting. It eliminates the quantization noise caused by discrete sampling and significantly improves the robustness of broadband beam control.

[0036] Specifically, in this embodiment of the invention, the step of quantizing and mapping the theoretical phase spectrum based on the matching error to obtain the phase control code includes: obtaining the first fundamental phase spectrum of the first conduction state and the second fundamental phase spectrum of the second cutoff state according to the broadband frequency response database; calculating the first matching error between the theoretical phase spectrum and the first fundamental phase spectrum, and the second matching error between the theoretical phase spectrum and the second fundamental phase spectrum; comparing the first matching error and the second matching error, and if the first matching error is less than the second matching error, then determining the control code of the first fundamental phase spectrum as the phase control code; if the first matching error is greater than the second matching error, then determining the control code of the second fundamental phase spectrum as the phase control code.

[0037] In a specific embodiment of the present invention, firstly, based on a pre-built broadband frequency response database, the full-band phase response data of the broadband dual-polarization unit under two distinct physical bias states are retrieved. The first conduction state corresponds to the conduction state of the switching component, for example, a bias voltage of 1.33V. In this state, the unit exhibits electric dipole resonance characteristics and provides approximately 180 degrees of reflection phase. The second cutoff state corresponds to the cutoff state of the switching component, for example, a bias voltage of 0V. In this state, the unit exhibits magnetic dipole resonance characteristics and provides approximately 0 degrees of reflection phase. Subsequently, based on the theoretical phase spectrum calculated in the aforementioned steps, two independent error calculation processes are executed. The first calculation calculates the phase difference between the theoretical phase spectrum and the first fundamental phase spectrum at each frequency sampling point by weighted summation, thereby obtaining a scalar value as the first matching error. This value represents the error if the unit is forcibly set to conduction. The first matching error is calculated by comparing the theoretical phase spectrum with the second fundamental phase spectrum across the entire broadband range. Then, a numerical comparison operation is performed at the digital logic level, comparing the first and second matching errors. If the first matching error is smaller, it indicates that the conduction state is closer to the theoretical beam requirement in the broadband frequency domain, and the system locks the binary code of the corresponding conduction state (e.g., logic "1") as the final output. Conversely, if the second matching error is smaller, the cutoff state is determined as the current optimal solution, and the binary code of the corresponding cutoff state (e.g., logic "0") is determined as the output. Finally, the selected phase control code is sent to the corresponding broadband dual-polarization unit bias circuit through the FPGA array's IO port, driving the switching components to switch to the selected physical operating state, completing the physical modulation of the electromagnetic wave.

[0038] More specifically, such as Figure 8 As shown in a specific embodiment of the present invention, Figure 8The electromagnetic simulation characteristics of the broadband dual-polarization unit in both ON and OFF physical states are shown. The horizontal axis of the figure represents the operating frequency (approximately 7 GHz to 13 GHz), the left vertical axis represents the reflection amplitude (0 dB to -35 dB), and the right vertical axis represents the reflection phase (-200° to 250°). The reading rules are clearly indicated by arrows in the figure: the upper left arrow indicates that the solid line data refers to the left axis, showing that the unit has low loss characteristics in both states; the lower right arrow indicates that the dashed line data refers to the right axis. It is particularly noteworthy that the phase difference curve (i.e., the black dashed line) is highlighted and marked by the black dashed ellipse on the right side of the figure. Combined with the effective operating bandwidth (approximately 8.8 GHz to 12.1 GHz) indicated by the light blue shaded area and the two cyan horizontal dashed lines (the 160° and 200° boundaries), it can be seen that the unit always maintains a phase difference range of 180° ± 20° within the broadband range, which fully verifies its stable broadband 1-bit phase modulation capability.

[0039] Specifically, in a specific embodiment of the present invention, the step of calculating the theoretical phase spectrum of each broadband dual-polarization unit includes: establishing a spatial coordinate system for the reflector antenna and obtaining the spatial position coordinates of each broadband dual-polarization unit in the spatial coordinate system; determining the wave vector of the target beam according to the target beam pointing command and calculating the spatial path difference between the wave vector and each spatial position coordinate; converting the spatial path difference into a phase delay based on the frequency sampling points, and combining the phase delays of each frequency sampling point to generate the theoretical phase spectrum.

[0040] In a specific embodiment of the present invention, a Cartesian coordinate system is first constructed with the geometric center of the reflective array as the origin, and the plane in which the array is located is set as the XOY plane with the normal direction as the Z-axis. Based on the array design parameters, the array size is set to 16 rows by 16 columns, and the unit period is 14.5 mm. For any broadband dual-polarized unit in the m-th row and n-th column of the array, the spatial position coordinates of its geometric center are calculated according to its index value in the array, thereby determining the physical position of each unit relative to the phase reference center. Subsequently, the target beam pointing command is parsed, the elevation angle and azimuth angle of the target beam are extracted, the wave vector direction of the target beam is determined according to the plane wave approximation principle, and the spatial path difference generated when the wave vector is projected onto each unit position is calculated. The formula for calculating the spatial path difference is as follows: ; in, Indicates spatial path difference, Represents the x-coordinate of the cell. Represents the ordinate of the element. Indicates the elevation angle of the target beam. This represents the azimuth angle of the target beam. Next, the frequency domain conversion stage begins. Within the operating frequency band of 8.8 GHz to 12.1 GHz, based on several frequency sampling points determined through discretization, the spatial path difference calculated above is converted into corresponding phase delay values ​​using phase delay calculation logic. This calculation logic states that the phase delay equals the spatial path difference multiplied by twice pi, multiplied by the current sampling frequency, and finally divided by the speed of light. Finally, the phase delay values ​​calculated from all frequency sampling points are arranged and combined according to frequency order to generate a theoretical phase spectrum vector specific to this unit. This vector precisely describes the ideal phase compensation value that this physical unit should provide in order to ensure that electromagnetic waves of different frequencies are superimposed in phase at the same point in space.

[0041] Specifically, in a specific embodiment of the present invention, the step of decomposing the target beam pointing command into a first polarization control vector and a second polarization control vector includes: obtaining the first polarization direction corresponding to the first polarization port of the broadband dual polarization unit and the second polarization direction corresponding to the second polarization port; orthogonally projecting the target electric field vector corresponding to the target beam pointing command onto the first polarization direction and the second polarization direction respectively, to obtain the first polarization control vector projected onto the first polarization direction and the second polarization control vector projected onto the second polarization direction.

[0042] In this embodiment of the invention, a polarization reference coordinate system strictly corresponding to the physical structure of the broadband dual-polarization unit is first established. Based on the layout characteristics of the metal layer on the unit surface, the axial extension direction of the first pair of bowtie dipoles is defined as the first polarization direction, i.e., the X-axis direction, and the axial extension direction of the second pair of bowtie dipoles perpendicular to them is defined as the second polarization direction, i.e., the Y-axis direction, thereby determining the polarization basis vector of the physical port. After receiving the target beam pointing command containing the spatial angle and polarization state, the system does not directly treat it as a single scalar, but constructs it as an electric field vector in the target space based on electromagnetic field theory. Then, orthogonal projection operation is performed to calculate the target electric field vector and the first polarization direction. The dot product of unit vectors, i.e., obtaining the projection component of the target vector on the X-axis, is used as the first polarization control vector. This vector represents the magnitude and phase of the electric field component that the dipole in the X-axis direction needs to contribute in order to synthesize the target beam. Simultaneously, the dot product of the target electric field vector and the unit vector in the second polarization direction is calculated to obtain its projection component on the Y-axis as the second polarization control vector. Through this decomposition mechanism, regardless of whether the target command requests a horizontally polarized, vertically polarized, 45-degree obliquely polarized, or circularly polarized beam, the system can decompose it into two orthogonal scalar commands that can be independently executed by physical hardware. This ensures that the subsequent generation of phase control codes can drive the switching component networks of the X-axis and Y-axis respectively, realizing beam polarization synthesis at the physical level.

[0043] like Figures 9 to 12As shown, to verify the effectiveness and polarization isolation of the above-mentioned vector orthogonal decomposition mechanism at the physical level, a simulation analysis of the surface current distribution was performed based on a broadband dual-polarization unit. The surface current vector distribution of the unit under both on and off states of the switching component is shown when a vertical (Y-polarization) excitation is applied. Experimental data show that when the switching component is on, the current distribution on the dipole is in the same direction as the ground current distribution, exhibiting electric dipole resonance characteristics and generating a 180-degree phase. When the switching component is off, the dipole current is in the opposite direction to the ground current, forming a loop, i.e., a magnetic dipole. The resonant characteristics generate a 0-degree phase. Most importantly, regardless of the state, although there is induced current on the dipole arm in the horizontal direction (X-polarization direction) of the figure, the current flows in opposite directions and cancels each other out in the far-field radiation, without forming an effective X-polarization radiation component. This experimental phenomenon intuitively proves that the broadband dual-polarization unit of the present invention has natural orthogonal isolation characteristics in its physical structure and there is no significant polarization crosstalk. This strongly demonstrates the physical correctness of the processing method of decomposing the target beam command into orthogonal control vectors, ensuring that the two polarization channels can be independently controlled without interfering with each other.

[0044] Specifically, in the embodiments of the present invention, the step of establishing a broadband frequency response database includes: configuring a broadband dual-polarization unit to a first conduction state and a second cutoff state, and establishing a first phase control code corresponding to the first conduction state and a second phase control code corresponding to the second cutoff state; performing electromagnetic simulation on the broadband dual-polarization unit to obtain the basic phase spectrum and simulated gain data of the broadband dual-polarization unit in the first conduction state, and the basic phase spectrum and simulated gain data in the second cutoff state; establishing a mapping index relationship between the basic phase spectrum, simulated gain data and phase control code, and constructing a broadband frequency response database based on the mapping index relationship.

[0045] In a specific embodiment of this invention, the physical model of the broadband dual-polarization unit needs to be accurately established in the full-wave electromagnetic simulation software first. The dielectric layer properties are set according to the parameters in the technical disclosure: the top layer uses Arlon AD350A with a relative permittivity of 3.5, the middle adhesive layer uses Rogers 4450F with a relative permittivity of 3.7, and the bottom layer uses FR-4. The equivalent circuit of the lumped element of the switching component in two operating states is defined. The first conducting state is set as an equivalent model of a 7.8Ω resistor and a 30pH inductor in series, corresponding to the binary phase control code "1". The second cutoff state is set as an equivalent model of an inductor of 30pH and a 25fF capacitor in series, corresponding to the binary phase control code "0". Then, simulation boundary conditions are set. Periodic boundary conditions are applied in the X and Y axes of the unit to simulate an infinite array environment. A Floquet port is set in the Z axis direction for excitation. The frequency scanning range is set to cover 8.8GHz to 12.1GHz, with a step size of 0.1G. Hz; then the simulation solver is started, and frequency sweep calculations are performed on the physical models corresponding to control codes "1" and "0" respectively. The complex S-parameter data at each frequency sampling point is extracted, and the simulation gain data (i.e., reflection loss) is obtained by calculating the amplitude of the S-parameters. The fundamental phase spectrum is obtained by calculating the phase angle of the S-parameters, thus obtaining two complete frequency domain response datasets. Finally, a structured data table with frequency and control code as joint indexes is constructed, and the phase value and gain value obtained above are filled into the corresponding index positions as keys, completing the encapsulation of the broadband frequency response database. This database can provide high-precision physical layer data support for subsequent error calculation and beamforming.

[0046] The present invention also provides a control system for a reflective array antenna based on a broadband dual-polarization unit. The system is used to execute the above-described control method for a reflective array antenna based on a broadband dual-polarization unit, including: The array antenna surface is composed of several broadband dual-polarization elements arranged periodically. The control module is electrically connected to each broadband dual-polarization unit in the array antenna surface and is used to execute the control method of the reflective array antenna based on the broadband dual-polarization unit.

[0047] Specifically, in an embodiment of the present invention, the broadband dual-polarization unit includes: a dielectric layer 1, which includes a top dielectric layer 101, a middle dielectric layer 102, and a bottom dielectric layer 103 arranged sequentially at intervals; a radiation layer 2 is provided at the upper end of the top dielectric layer 101, which includes a dipole group 201, a grounding patch 202, and a switching assembly 203; there are two dipole groups 201, with two dipoles 201a in the same group arranged opposite each other, and the four dipoles 201a of the two pairs of dipole groups 201 arranged orthogonally; the grounding patch 202 is disposed between the two dipoles 201a of the dipole group 201 and is connected to the grounding patch 202. The switching assembly 203 is connected to the dipole 201a; a grounding metal layer 301 is provided between the top dielectric layer 101 and the middle dielectric layer 102, a choke metal layer 302 is provided between the middle dielectric layer 102 and the bottom dielectric layer 103, and a bias metal layer 303 is provided on the lower surface of the bottom dielectric layer 103; wherein, the grounding patch 202 passes downward through the top dielectric layer 101 and is connected to the grounding metal layer 301; the dipole 201a passes through the grounding metal layer 301 through the metallized via 4 and is insulated from the grounding metal layer 301, and the dipole 201a is electrically connected downward to the choke metal layer 302 and the bias metal layer 303.

[0048] As described above, the present invention relates to a control method for a reflective array antenna based on a broadband dual-polarization unit, which can overcome the shortcomings of traditional reflective array antennas, such as severe polarization component coupling, low phase matching degree in the broadband range, and inaccurate phase control code acquisition. It significantly enhances the independent pointing accuracy and full-band gain stability of the dual-polarization beam, thereby realizing flexible beam reconstruction in the polarization and frequency dimensions. The method for a reflective array antenna based on a broadband dual-polarization unit includes: S1 acquiring a target beam pointing command and decomposing the target beam pointing command into a first polarization control vector and a second polarization control vector, wherein the first polarization control vector and the second polarization control vector are orthogonal to each other; S2 calculating the theoretical phase spectrum of each broadband dual-polarization unit based on the first polarization control vector and the second polarization control vector; S3 extracting the fundamental phase spectrum of the broadband dual-polarization unit based on a preset broadband frequency response database; S4 calculating the matching error between the theoretical phase spectrum of each broadband dual-polarization unit and the fundamental phase spectrum, and quantizing and mapping the theoretical phase spectrum based on the matching error to obtain a phase control code, wherein the phase control code includes a first polarization phase control code and a second polarization phase control code; wherein the broadband dual-polarization unit has two sets of orthogonally arranged dipole groups, and the physical operating states of the dipole groups include a first conduction state and a second cutoff state; the phase control code is used to drive the physical operating state of the dipole groups to switch to the physical operating state corresponding to the phase control code.Specifically, by acquiring the target beam pointing command and decomposing it into mutually orthogonal first and second polarization control vectors, this vector orthogonal decomposition mechanism breaks through the logical barrier of mutual constraint between components in existing dual-polarization beam control technologies. It establishes an independent decoupling framework for the polarization dimension, effectively solving the problem of severe polarization component coupling during beam control of traditional reflector array antennas. Secondly, by calculating the theoretical phase spectrum of each broadband dual-polarization unit based on the polarization control vectors and extracting the fundamental phase spectrum from a pre-set database, a global comparison system between the full-band spectrum and the fundamental response is constructed in the frequency domain. This provides a continuous observation window for phase consistency across the broadband range, preventing performance degradation at the bandwidth edges due to reliance on single-frequency phase design and significantly enhancing the system's performance. The invention achieves precise alignment between theoretical beam requirements and physical unit states by utilizing a mechanism that calculates the matching error between the theoretical phase spectrum and the fundamental phase spectrum and performs quantization mapping based on this error. This ensures that the final acquired phase control code can drive the broadband dual-polarization unit to switch to the physical operating state with minimal error, avoiding mapping distortion caused by the lack of error optimization in traditional schemes, thereby significantly improving the accuracy of phase control code acquisition. Compared with existing technologies, this invention overcomes the shortcomings of traditional reflective array antennas, such as severe polarization component coupling, low phase matching within the broadband range, and inaccurate phase control code acquisition. It significantly enhances the independent pointing accuracy and full-band gain stability of the dual-polarization beam, thereby achieving flexible beam reconstruction in the polarization and frequency dimensions.

[0049] The above description of the disclosed embodiments enables those skilled in the art to make or use the invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the general principles defined herein may be implemented in other embodiments without departing from the spirit or scope of the invention. Therefore, the invention is not to be limited to the embodiments shown herein, but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims

1. A control method for a reflective array antenna based on a broadband dual-polarization unit, characterized in that, include: S1 acquires the target beam pointing command and decomposes the target beam pointing command into a first polarization control vector and a second polarization control vector, wherein the first polarization control vector and the second polarization control vector are orthogonal to each other; S2 calculates the theoretical phase spectrum of each broadband dual-polarization unit based on the first polarization control vector and the second polarization control vector; S3 extracts the fundamental phase spectrum of the broadband dual-polarization unit according to the preset broadband frequency response database; S4 calculates the matching error between the theoretical phase spectrum and the basic phase spectrum of each broadband dual-polarization unit, and performs quantization mapping on the theoretical phase spectrum based on the matching error to obtain the phase control code, which includes a first polarization phase control code and a second polarization phase control code. The broadband dual-polarization unit has two sets of orthogonally arranged dipole groups, and the physical working states of the dipole groups include a first on state and a second off state. The phase control code is used to drive the physical operating state of the dipole group to switch to the physical operating state corresponding to the phase control code.

2. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 1, characterized in that, The step of calculating the matching error between the theoretical phase spectrum and the fundamental phase spectrum of each broadband dual-polarization unit includes: The operating frequency band of the broadband dual-polarization unit is obtained, and the operating frequency band is discretized to obtain several frequency sampling points; The theoretical compensated phase and physical phase response of each frequency sampling point are obtained respectively, and the original phase difference between the theoretical compensated phase and the physical phase response at each frequency sampling point is calculated. Based on each of the frequency sampling points, the absolute value of the original phase difference is weighted to obtain the weighted phase error component; The weighted phase error components corresponding to each frequency sampling point are summed to obtain the matching error.

3. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 2, characterized in that, The step of weighting the absolute value of the original phase difference includes: Obtain the center frequency of the operating frequency band, and calculate the absolute value of the frequency deviation between each frequency sampling point and the center frequency value; The absolute value of the frequency deviation is mapped according to a preset attenuation function to obtain the frequency weighting coefficient corresponding to each frequency sampling point; The weighted phase error component is obtained by multiplying the absolute value of the original phase difference with the corresponding frequency weighting coefficient.

4. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 3, characterized in that, The steps for constructing the attenuation function include: The broadband frequency response database is invoked to extract the simulated gain data of the broadband dual-polarization unit in the operating frequency band, and a gain-frequency response curve is constructed based on the simulated gain data. Extract the maximum gain value of the gain frequency response curve at the center frequency, and normalize the gain frequency response curve according to the maximum gain value to obtain the normalized gain distribution. The attenuation function is obtained by fitting the normalized gain distribution to a function.

5. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 2, characterized in that, The step involves quantizing and mapping the theoretical phase spectrum based on the matching error to obtain the phase control code, including: The first fundamental phase spectrum of the first conduction state and the second fundamental phase spectrum of the second cutoff state are obtained from the broadband frequency response database. Calculate the first matching error between the theoretical phase spectrum and the first basic phase spectrum, and the second matching error between the theoretical phase spectrum and the second basic phase spectrum, respectively. The first matching error is compared with the second matching error. If the first matching error is less than the second matching error, the control code of the first basic phase spectrum is determined as the phase control code. If the first matching error is greater than the second matching error, then the control code of the second basic phase spectrum is determined as the phase control code.

6. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 1, characterized in that, The steps for calculating the theoretical phase spectrum of each broadband dual-polarization unit include: Establish a spatial coordinate system for the reflective array antenna and obtain the spatial position coordinates of each broadband dual-polarization unit in the spatial coordinate system; The wave vector of the target beam is determined according to the target beam pointing command, and the spatial path difference between the wave vector and each of the spatial position coordinates is calculated. The spatial path difference is converted into a phase delay based on the frequency sampling points, and the phase delays of each frequency sampling point are combined to generate a theoretical phase spectrum.

7. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 1, characterized in that, The target beam pointing command described in step [step] is decomposed into a first polarization control vector and a second polarization control vector, including: Obtain the first polarization direction corresponding to the first polarization port of the broadband dual polarization unit, and the second polarization direction corresponding to the second polarization port; The target electric field vector corresponding to the target beam pointing command is orthogonally projected onto the first polarization direction and the second polarization direction, respectively, to obtain the first polarization control vector projected onto the first polarization direction and the second polarization control vector projected onto the second polarization direction.

8. The control method for a reflective array antenna based on a broadband dual-polarization unit according to claim 1, characterized in that, The steps for establishing the broadband frequency response database include: The broadband dual-polarization unit is configured to a first on state and a second off state, and a first phase control code corresponding to the first on state and a second phase control code corresponding to the second off state are established. Electromagnetic simulation was performed on the broadband dual-polarization unit to obtain the basic phase spectrum and simulation gain data of the broadband dual-polarization unit in the first conduction state, and the basic phase spectrum and simulation gain data in the second cutoff state. Establish a mapping index relationship between the basic phase spectrum, the simulated gain data and the phase control code, and construct a broadband frequency response database based on the mapping index relationship.

9. A control system for a reflective array antenna based on a broadband dual-polarization unit, characterized in that, The system is used to execute the reflective array antenna control method based on broadband dual-polarization units according to any one of claims 1 to 8, and the system comprises: An array antenna surface, which is composed of a number of broadband dual-polarization units arranged periodically; A control module is electrically connected to each of the broadband dual-polarization units in the array antenna surface, and is used to execute the reflective array antenna control method based on broadband dual-polarization units.

10. The reflective array antenna control system based on a broadband dual-polarization unit according to claim 9, characterized in that, The broadband dual-polarization unit includes: The dielectric layer (1) includes a top dielectric layer (101), a middle dielectric layer (102) and a bottom dielectric layer (103) arranged sequentially at intervals. The top dielectric layer (101) has a radiation layer (2) at its upper end. The radiation layer (2) includes a dipole group (201), a grounding patch (202), and a switching assembly (203). The number of dipole groups (201) is 2 groups, with the two dipoles (201a) in the same group arranged opposite each other, and the four dipoles (201a) of the two pairs of dipole groups (201) arranged orthogonally. The grounding patch (202) is disposed between the two dipoles (201a) of the dipole group (201) and is connected to the dipoles (201a) through the switch assembly (203); A grounding metal layer (301) is provided between the top dielectric layer (101) and the middle dielectric layer (102), a choke metal layer (302) is provided between the middle dielectric layer (102) and the bottom dielectric layer (103), and a bias metal layer (303) is provided on the lower surface of the bottom dielectric layer (103). The grounding patch (202) extends downward through the top dielectric layer (101) and connects to the grounding metal layer (301); The dipole (201a) passes through the ground metal layer (301) through the metallized via (4) and is insulated from the ground metal layer (301). The dipole (201a) is electrically connected downward to the choke metal layer (302) and the bias metal layer (303).

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