LED display information matrix coding system based on distributed control

Abstract

The application relates to the technical field of LED display control, and particularly discloses an LED display information matrix coding system based on distributed control, which collects spatial coordinates of each sub-region and an overall pixel matrix; chaos initial values are allocated to each sub-region according to the spatial coordinates and are injected into a chaos oscillation loop to generate a local clock reference signal; the overall pixel matrix is decomposed into sub-matrices, and phase coding is embedded into the sub-matrices as synchronous time stamps to form coding data packets; each sub-region exchanges weakly coupled synchronous pulses through a coupling channel, and the phase is calibrated by using the chaos phase synchronization characteristic, so that all the local clock reference signals are aligned; when a preset common phase value is reached, the decoded sub-matrices are converted into driving current outputs to complete the whole-screen synchronous refreshing; and the application realizes nanosecond-level clock synchronization of distributed sub-regions and eliminates accumulated offset.

Description

Technical Field

[0001] This invention relates to the field of LED display control technology, and more specifically to an LED display information matrix encoding system based on distributed control. Background Technology

[0002] In the field of display device manufacturing, LED displays currently widely adopt a centralized control architecture. A main control card is responsible for receiving and processing the complete display image, sending the entire frame of pixel data sequentially to multiple cascaded driver chips via parallel or serial buses. Each driver chip has a shift register and a latch internally. Data is passed from the preceding chip to the following chip. After the entire frame of data is written to all shift registers, the main control card sends a unified latch signal, causing all chips to simultaneously output the corresponding voltage or current, driving the LED beads to emit light. This cascaded and global latching method can achieve basic display functions at conventional resolutions.

[0003] In a distributed LED display environment without a global master clock, with electromagnetic interference and local connection failures, how can each sub-region maintain nanosecond-level clock reference alignment autonomously by intermittently exchanging weak coupling synchronization pulses, thereby eliminating the accumulated phase offset inherent in traditional centralized cascaded architectures due to serial data transmission and global latching wait? Summary of the Invention

[0004] The purpose of this invention is to provide an LED display information matrix encoding system based on distributed control to solve the problems mentioned above.

[0005] The objective of this invention can be achieved through the following technical solutions:

[0006] An LED display information matrix encoding system based on distributed control includes a coordinate matrix acquisition module for acquiring the spatial coordinates of each sub-region and the overall pixel matrix of the image to be displayed.

[0007] The chaotic clock generation module assigns a set of chaotic initial values ​​to each sub-region based on spatial coordinates, and injects the chaotic initial values ​​into the local chaotic oscillation circuit of each sub-region to generate a local clock reference signal with initial value sensitivity.

[0008] The submatrix encoding and packaging module decomposes the overall pixel matrix into submatrices that correspond one-to-one with each sub-region based on spatial coordinates, and encodes the phase of the local clock reference signal into a synchronization timestamp and embeds it into the submatrix to form a timestamp-encoded data packet.

[0009] The pulse synchronization calibration module intermittently exchanges weak coupling synchronization pulses through the coupling channel in each sub-region. Utilizing the phase synchronization characteristics of the chaotic system, it continuously calibrates the phase of the chaotic oscillation circuit in the region based on the received coupling synchronization pulses and the synchronization timestamp in the local encoded data packet, so that the local clock reference signals of all sub-regions are aligned.

[0010] The phase-triggered output module converts the decoded sub-matrix into current outputs that drive each light-emitting element in parallel when the local clock reference signal of each sub-region reaches the preset common phase value, thus completing the synchronous refresh of the entire screen.

[0011] As a further aspect of the present invention: the process of generating the overall pixel matrix is ​​as follows:

[0012] A set of chaotically encoded test light pulses is sent to each sub-region, each test light pulse carrying a unique chaotic sequence identifier;

[0013] The response time series of the light-emitting elements in each sub-region to the test light pulse is collected. The response time series includes the phase difference information between the pulse arrival time and the local chaotic oscillation circuit.

[0014] Based on the cross-correlation peak positions of the response time series and the chaotic sequence, the relative spatial relationships between the sub-regions are inferred, thereby reconstructing the grayscale values ​​of each pixel in the overall pixel matrix of the image to be displayed.

[0015] As a further aspect of the present invention: the generation of a local clock reference signal with initial value sensitivity specifically includes:

[0016] The three-dimensional values ​​of the spatial coordinates are used as the initial voltage of the nonlinear capacitor, the initial current of the inductor, and the bias voltage of the negative resistance element in the chaotic oscillation circuit, respectively.

[0017] A transient impact pulse with a duration of one oscillation cycle is applied to the chaotic oscillation circuit, triggering the circuit to enter a chaotic oscillation state;

[0018] After the impact pulse ends, the amplitude values ​​of the first three oscillation peaks of the signal output by the acquisition circuit are collected. These three amplitude values ​​are arranged in sequence to form a set of initial chaotic values, which are then locked as the basis for generating the local clock reference signal.

[0019] As a further aspect of the present invention: applying a transient impact pulse with a duration of one oscillation cycle to the chaotic oscillation circuit specifically includes:

[0020] The output signals of the chaotic oscillation loops in two adjacent sub-regions are continuously acquired, and the instantaneous voltage difference between them is calculated.

[0021] When the absolute value of the instantaneous voltage difference exceeds the preset chaotic attractor boundary threshold, a pulse generation action is triggered;

[0022] Based on the current oscillation frequency of the local oscillation circuit, a complete oscillation period width is extracted as the duration of the transient impact pulse, and the transient impact pulse is injected into the local chaotic oscillation circuit.

[0023] As a further aspect of the present invention: the formation of the timestamped encoded data packet specifically includes:

[0024] Using the spatial coordinates of each sub-region as the initial value for the chaotic mapping iteration, a set of pseudo-random permutation indices is generated after a predetermined number of iterations.

[0025] The pixel grayscale values ​​at the corresponding positions are extracted from the overall pixel matrix according to the pseudo-random permutation index, and then sequentially filled into the sub-matrix of the corresponding sub-region.

[0026] The current phase value of the local clock reference signal is converted into a pulse interval duration. A positioning pulse corresponding to the pulse interval duration is inserted before the starting position of the sub-matrix to form a timestamped encoded data packet.

[0027] As a further aspect of the present invention: the step of extracting the pixel grayscale values ​​at corresponding positions from the overall pixel matrix according to the pseudo-random permutation index and sequentially filling them into the sub-matrix of the corresponding sub-region specifically includes:

[0028] The current output signal voltage value of the local chaotic oscillation circuit is quantized and used as the starting decimation position;

[0029] After extracting a pixel grayscale value each time, the state of the chaotic oscillation circuit is iterated once to generate the next extraction position;

[0030] When the number of extracted pixel grayscale values ​​reaches the preset size of the submatrix, the final state of the chaotic oscillation circuit is saved as the initial extraction seed for the next submatrix.

[0031] As a further aspect of the present invention: the continuous calibration of the phase of the chaotic oscillation circuit in this region, so that the local clock reference signals of all sub-regions are aligned, specifically includes:

[0032] Extract the actual arrival time of the weakly coupled synchronization pulse from the received weakly coupled synchronization pulse, and at the same time, parse the expected arrival time indicated by the synchronization timestamp corresponding to the weakly coupled synchronization pulse from the local encoded data packet.

[0033] Calculate the phase deviation between the actual arrival time and the expected arrival time, and convert the phase deviation into an error voltage;

[0034] An error voltage is applied to the varactor diode of the chaotic oscillation circuit in this region to change the instantaneous oscillation frequency of the circuit until the actual arrival time coincides with the expected arrival time, thus completing phase alignment.

[0035] As a further aspect of the present invention: the step of parsing the expected arrival time indicated by the synchronization timestamp corresponding to the weakly coupled synchronization pulse from the local encoded data packet specifically includes:

[0036] The output signal of the local chaotic oscillation loop at the current moment is used as a matching template and compared with the pre-set chaotic attractor trajectory in the encoded data packet in segments.

[0037] Each time a weak coupling synchronization pulse is received, a segment of the chaotic waveform within half an oscillation cycle before and after the arrival of the weak coupling synchronization pulse is extracted.

[0038] Perform a sliding cross-correlation operation between the waveform segment and the theoretical waveform corresponding to all candidate timestamps in the encoded data packet, and select the timestamp corresponding to the cross-correlation peak position as the expected arrival time.

[0039] As a further aspect of the present invention: the method of converting the decoded sub-matrix into parallel current outputs to drive each light-emitting element, thereby completing the synchronous refresh of the entire screen, specifically includes:

[0040] The instantaneous amplitude of the local clock reference signal is compared with the reference voltage corresponding to the preset common phase value, and a trigger edge is generated when the two are equal.

[0041] Based on the trigger edge, the grayscale value of each pixel in the decoded submatrix is ​​converted into a voltage pulse train of corresponding width;

[0042] The voltage pulse train is directly coupled to the anode of each light-emitting element through a set of parallel analog switches, so that the light-emitting elements are turned on within the pulse width, thus completing the synchronous refresh of the entire screen.

[0043] As a further aspect of the present invention: the step of converting the grayscale value of each pixel in the decoded sub-matrix into a voltage pulse train of corresponding width based on the trigger edge specifically includes:

[0044] Each pixel grayscale value in the decoded submatrix is ​​fed into a parallel comparator array driven by a local chaotic oscillation circuit. The parallel comparator array outputs a combination of high and low levels.

[0045] A linear ramp voltage generator is started using the trigger edge, and the rate of rise of the ramp voltage is determined by the oscillation frequency of the local chaotic oscillation circuit.

[0046] The high and low level combinations are compared with the ramp voltage step by step. When the ramp voltage reaches the threshold corresponding to each comparator, the output state is flipped, forming a voltage pulse train whose width is proportional to the gray value.

[0047] The beneficial effects of this invention are:

[0048] (1) In this invention, each sub-region uses a chaotic oscillation circuit to generate a local clock reference signal with initial value sensitivity, and intermittently exchanges weak coupling synchronization pulses through a coupling channel. The phase is continuously calibrated by utilizing the phase synchronization characteristics of the chaotic system, so that the local clock reference signals of all sub-regions are aligned to the nanosecond level. Compared with the traditional centralized architecture that relies on a single global latch signal and serial data shifting step by step, this invention can achieve parallel synchronous refresh of all sub-regions without waiting for the entire frame of data to be written, eliminating the cumulative phase offset caused by the length of the cascaded link and the data transmission delay, and ensuring strict synchronization of the images in each area of ​​the large splicing display screen.

[0049] (2) In this invention, each sub-region only needs to maintain chaotic synchronization by intermittently exchanging weak coupling synchronization pulses between adjacent nodes, without relying on the main control device to continuously send global latching signals or a dedicated clock synchronization protocol. When a sub-region is briefly disconnected from the main control or its coupling channel experiences a momentary interruption, the sub-region can still maintain the synchronization state of its own clock reference signal by relying on the chaotic coupling pulses with neighboring nodes, and quickly relock after the connection is restored. This distributed autonomous synchronization mechanism avoids the problem of single-point failure leading to the failure of all subsequent nodes in the traditional cascaded architecture, while reducing the stringent requirements for long-distance transmission of synchronization signals in complex electromagnetic environments, and improving the operational stability of the system in strong interference scenarios such as stadiums and stages. Attached Figure Description

[0050] The invention will now be further described with reference to the accompanying drawings.

[0051] Figure 1 This is a system block diagram of the present invention;

[0052] Figure 2 This is a flowchart of the synchronous refresh process of the entire screen in this invention. Detailed Implementation

[0053] The technical solutions of the embodiments of the present invention will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of the present invention, and not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0054] Example 1, please refer to Figure 1As shown, the present invention is an LED display information matrix encoding system based on distributed control, comprising:

[0055] The coordinate matrix acquisition module is used to acquire the spatial coordinates of each sub-region and the overall pixel matrix of the image to be displayed.

[0056] The chaotic clock generation module assigns a set of chaotic initial values ​​to each sub-region based on spatial coordinates, and injects the chaotic initial values ​​into the local chaotic oscillation circuit of each sub-region to generate a local clock reference signal with initial value sensitivity.

[0057] The submatrix encoding and packaging module decomposes the overall pixel matrix into submatrices that correspond one-to-one with each sub-region based on spatial coordinates, and encodes the phase of the local clock reference signal into a synchronization timestamp and embeds it into the submatrix to form a timestamp-encoded data packet.

[0058] The pulse synchronization calibration module intermittently exchanges weak coupling synchronization pulses through the coupling channel in each sub-region. Utilizing the phase synchronization characteristics of the chaotic system, it continuously calibrates the phase of the chaotic oscillation circuit in the region based on the received coupling synchronization pulses and the synchronization timestamp in the local encoded data packet, so that the local clock reference signals of all sub-regions are aligned.

[0059] The phase-triggered output module converts the decoded sub-matrix into current outputs that drive each light-emitting element in parallel when the local clock reference signal of each sub-region reaches the preset common phase value, thus completing the synchronous refresh of the entire screen.

[0060] Example 2: In the coordinate matrix acquisition module, the spatial coordinates of each sub-region and the overall pixel matrix of the image to be displayed are acquired, specifically including:

[0061] Each sub-region is assigned a unique chaotic sequence identifier, which consists of a 127-bit binary pseudo-random code at a chip rate of 10 MHz. This chaotic sequence identifier is modulated onto a 650 nm red light carrier wave via an electro-optic conversion circuit to form a chaotically coded test light pulse. The duration of each test light pulse is 12.7 microseconds, equal to the period of a complete chaotic sequence.

[0062] The light-emitting elements in each sub-region are controlled to be in a reverse bias state simultaneously when receiving the test light pulse, enabling them to function as photodetectors. In each sub-region, a voltage comparator is pre-set, with its threshold set to three times the dark-state noise voltage of the light-emitting element. When the test light pulse arrives, the photocurrent generated by the light-emitting element is converted into a voltage signal by a transimpedance amplifier. Once this voltage exceeds the comparator threshold, this moment is recorded as the pulse arrival time.

[0063] In each sub-region, the instantaneous output voltage of the local chaotic oscillation circuit is synchronously acquired. This voltage is then digitized by an analog-to-digital converter at a sampling rate of 100 MHz to obtain continuous phase difference information. The phase value of the local chaotic oscillation circuit corresponding to the pulse arrival time is subtracted from the reference phase value when the test optical pulse is transmitted to obtain the phase difference of that sub-region. This phase difference ranges from 0 to 360 degrees.

[0064] The response time series collected from all sub-regions are cross-correlated with their corresponding chaotic sequence identifiers. The specific steps of the cross-correlation operation are as follows: the response time series are discretized at 10 nanosecond intervals to obtain a discrete point sequence; the chaotic sequence identifiers are expanded at equal intervals, then multiplied point by point and accumulated. The position of the maximum value of the accumulated result is the position of the cross-correlation peak, which corresponds to the propagation delay of the test optical pulse between sub-regions.

[0065] The relative distance between two sub-regions is calculated based on the positions of the cross-correlation peaks. The actual spatial distance is obtained by subtracting the propagation constant of the light pulse in air (3.33 nanoseconds per meter) from the time delay value corresponding to the cross-correlation peak positions. This process is repeated, using one of the sub-regions as the origin, and triangulation is used to calculate the spatial coordinates of all sub-regions in a two-dimensional plane with millimeter-level accuracy.

[0066] Based on the spatial coordinates of each sub-region, the overall pixel matrix of the image to be displayed is reverse-mapped. For each pixel in the overall pixel matrix, the grayscale value corresponding to that pixel is calculated based on the spatial coordinates of its sub-region and the physical spacing of the light-emitting elements in that sub-region. The grayscale values ​​of all sub-regions are concatenated according to their spatial coordinates to reconstruct the complete overall pixel matrix. The number of rows in this matrix equals the total number of light-emitting elements in the vertical direction of all sub-regions, and the number of columns equals the total number of light-emitting elements in the horizontal direction.

[0067] Example 3: In the chaotic clock generation module, a set of initial chaotic values ​​is assigned to each sub-region based on spatial coordinates, and these initial chaotic values ​​are injected into the local chaotic oscillation circuit of each sub-region to generate a local clock reference signal with initial value sensitivity. Specifically, this includes:

[0068] The spatial coordinates of each sub-region are decomposed into three values: the first value represents the horizontal position number of the sub-region, the second value represents the vertical position number, and the third value represents the depth number of the sub-region relative to a preset reference point. These three values ​​are assigned to three components in the chaotic oscillation circuit: the first value serves as the initial voltage of the nonlinear capacitor, measured in volts, with a range of 0 to 5 volts; the second value serves as the initial current of the inductor, measured in amperes, with a range of 0 to 0.1 amperes; and the third value serves as the bias voltage of the negative resistance component, measured in volts, with a range of -2 volts to +2 volts. These three components are connected in parallel, forming the core of the chaotic oscillation circuit.

[0069] A transient impulse pulse with a duration of one oscillation cycle is applied to the chaotic oscillation circuit. The amplitude of this pulse is set to twice the initial voltage value of the nonlinear capacitor. The rise time and fall time of the pulse are both 1 nanosecond, and the pulse shape is an isosceles triangle. The pulse is applied by connecting a controllable switch in parallel across the nonlinear capacitor. When the switch is closed, an external energy storage capacitor discharges into the nonlinear capacitor through the switch, generating the desired transient impulse pulse. The on-time of the switch is controlled by a monostable multivibrator, the time constant of which is preset to be twice the expected oscillation period of the chaotic oscillation circuit.

[0070] After the impulse pulse ends, a peak hold circuit is used to continuously acquire the amplitude values ​​of the first three oscillation peaks of the chaotic oscillation loop output signal. The peak hold circuit consists of an operational amplifier and a holding capacitor; its reset signal is triggered by the falling edge of the impulse pulse, and after reset, it begins acquiring the first peak value. The amplitude value of the first peak is recorded as the first initial value, the amplitude value of the second peak as the second initial value, and the amplitude value of the third peak as the third initial value. These three amplitude values ​​are arranged sequentially according to the acquisition order, forming a set of chaotic initial values ​​containing three values. This set of chaotic initial values ​​is simultaneously locked into a three-way parallel register, serving as the sole basis for the subsequent generation of the local clock reference signal.

[0071] The output signals of chaotic oscillation loops in two adjacent sub-regions are continuously acquired, with the sampling frequency set to 10 times the highest oscillation frequency of the chaotic oscillation loop, i.e., 100 MHz. The two output signals are then fed into two identical analog-to-digital converters to obtain their respective instantaneous voltage values. These two instantaneous voltage values ​​are then input into a subtractor circuit, which outputs the difference between the two values. This difference changes continuously over time, forming a sequence of instantaneous voltage difference values.

[0072] A boundary threshold for the chaotic attractor is preset. The specific value of this threshold is determined as follows: when the chaotic oscillation circuit is operating normally, the maximum trajectory range of its output signal in phase space is measured, and 70% of the radial length of this range is taken as the boundary threshold. When the absolute value of the instantaneous voltage difference output by the subtractor exceeds this boundary threshold, the comparator outputs a high-level signal. This high-level signal triggers a monostable pulse generator to generate a trigger pulse with a width of 10 nanoseconds, serving as the start flag for pulse generation.

[0073] Simultaneously with the generation of the trigger pulse, the current output voltage waveform of the local chaotic oscillation circuit is sampled. A zero-crossing detection circuit is used to measure the time interval between two adjacent positive zero-crossing points; this time interval is the current oscillation period width. This time interval is then extracted as the duration of a complete oscillation period. The aforementioned trigger pulse is passed through a controllable delay line, delayed by a fixed transmission delay, and then injected into a pulse shaping circuit. The pulse shaping circuit outputs a square wave pulse with a constant amplitude and a width equal to the oscillation period width. This square wave pulse is injected into the local chaotic oscillation circuit as a transient impulse pulse, completing one full phase calibration operation.

[0074] Example 4: In the sub-matrix encoding and packaging module, based on spatial coordinates, the overall pixel matrix is ​​decomposed into sub-matrices corresponding one-to-one with each sub-region. The phase of the local clock reference signal is encoded as a synchronization timestamp and embedded in the sub-matrix to form a timestamped encoded data packet. Specifically, this includes:

[0075] The spatial coordinates of each sub-region are used as the initial values ​​for the chaotic mapping iteration. Here, the chaotic mapping uses a logistic mapping, whose iterative formula is: the next state value equals the current state value multiplied by one minus the difference between the current state value and a control parameter. The control parameter is set to 3.9, and the initial values ​​are the three spatial coordinate values ​​normalized to between 0 and 1. A predetermined number of iterations is performed, set to 100. After iteration, a pseudo-random sequence of length 100 is obtained. Each value in this sequence is multiplied by the total number of pixels in the overall pixel matrix and rounded to obtain a pseudo-random permutation index.

[0076] The pixel grayscale value is extracted from the overall pixel matrix according to the pseudo-random permutation index. The overall pixel matrix is ​​stored as a one-dimensional array in row-major order, and each pixel grayscale value is an integer between 0 and 255. Each value in the pseudo-random permutation index points to a position in this one-dimensional array, and the grayscale value at that position is extracted. A number of grayscale values ​​equal to the preset size of the submatrix are extracted sequentially, arranged in the extraction order, and filled into the submatrix of the sub-region. The preset size of the submatrix is ​​determined by the number of light-emitting elements in the sub-region. For example, if there are 128 elements horizontally and 64 elements vertically, the preset size of the submatrix is ​​8192 grayscale values.

[0077] The current phase value of the local clock reference signal is converted into the pulse interval duration. The local clock reference signal is a periodic triangular wave with a period of 1 microsecond. The phase value is represented by the ratio of the current voltage value of the triangular wave to the peak voltage, ranging from 0 to 1. The pulse interval duration is calculated by multiplying the phase value by the period duration, which gives the time interval from the start of the previous synchronization pulse to the current moment, in nanoseconds. For example, when the phase value is 0.25, the pulse interval duration is 250 nanoseconds.

[0078] A positioning pulse corresponding to the pulse interval duration is inserted before the starting position of the sub-matrix. The structure of the encoded data packet is as follows: first, a start identifier pulse with a width of 100 nanoseconds is sent; then, after waiting for the previously calculated pulse interval duration, a positioning pulse with a width of 50 nanoseconds is sent; finally, all grayscale value data of the sub-matrix is ​​sent. The arrival time of the positioning pulse serves as the synchronization timestamp of the sub-matrix. All grayscale value data uses non-return-to-zero encoding, with each grayscale value represented by 8 bits, and the least significant bits are sent serially first.

[0079] The current output signal voltage value of the local chaotic oscillation loop is quantized and used as the starting decimation position. The voltage range of the local chaotic oscillation loop output signal is -5V to +5V, which is quantized into an integer between 0 and 1023 using an analog-to-digital converter. The remainder of this integer divided by the total number of pixels in the overall pixel matrix is ​​used as the first decimation position. After each pixel grayscale value is decimated, the state of the chaotic oscillation loop is iterated once. The iteration method is as follows: the nonlinear capacitor voltage and inductor current in the current loop are used as state variables, and a numerical integration with a step size of 10 nanoseconds is performed according to the differential equation of the chaotic oscillation loop. The integration result is used as the new state variable, and its output voltage value is then quantized to obtain the next decimation position.

[0080] When the number of extracted pixel grayscale values ​​reaches the preset size of the submatrix, the final state of the chaotic oscillation loop is saved as the initial extraction seed for the next submatrix. Specifically, the voltage value of the nonlinear capacitor and the current value of the inductor in the chaotic oscillation loop are recorded and stored in two separate 16-bit registers. When extraction is needed for the next submatrix, these two stored values ​​are reloaded into the chaotic oscillation loop as the initial state, eliminating the need to regenerate initial values ​​from spatial coordinates. This ensures that the extraction sequence between adjacent submatrices exhibits continuous chaotic characteristics while reducing the computational burden of repeated iterations.

[0081] Example 5, please refer to Figure 2 As shown, in the pulse synchronization calibration module, each sub-region intermittently exchanges weak coupling synchronization pulses through a coupling channel. Utilizing the phase synchronization characteristics of the chaotic system, the phase of the chaotic oscillation circuit in this region is continuously calibrated based on the received coupling synchronization pulses and the synchronization timestamp in the local encoded data packet, thereby aligning the local clock reference signals of all sub-regions. Specifically, this includes:

[0082] The actual arrival time of the received weakly coupled synchronization pulse is extracted. Specifically, a high-speed comparator is set at the input of each sub-region, with its reference voltage set to half the peak amplitude of the weakly coupled synchronization pulse. When the rising edge of the weakly coupled synchronization pulse crosses this reference voltage, the comparator outputs a transition signal. This transition signal triggers a time-to-digital converter to record the count value of the local clock reference signal at this moment. The time-to-digital converter has a resolution of 1 nanosecond; the recorded count value multiplied by 1 nanosecond gives the actual arrival time, which is recorded as the actual time value.

[0083] Simultaneously, the expected arrival time indicated by the synchronization timestamp corresponding to the weakly coupled synchronization pulse is parsed from the local encoded data packet. The parsing process consists of the following three sub-steps: First, the output signal of the local chaotic oscillation loop at the current moment is used as the matching template. This output signal is a waveform of voltage changing with time, with a sampling rate of 1 GHz. Each time, a waveform segment with a length of 100 nanoseconds is taken as the template. Second, for each weakly coupled synchronization pulse received, chaotic waveform segments within half an oscillation period before and after the arrival of the pulse are extracted. The oscillation period is determined by the center frequency of the local chaotic oscillation loop, which is 10 MHz. Therefore, half an oscillation period is 50 nanoseconds, and the total length of the extracted waveform segments is 100 nanoseconds. Finally, a sliding cross-correlation operation is performed between the extracted waveform segments and the theoretical waveforms corresponding to all candidate timestamps in the encoded data packet. The timestamp corresponding to the cross-correlation peak position is selected as the expected arrival time.

[0084] The phase deviation between the actual arrival time and the expected arrival time is calculated and converted into an error voltage. The formula for calculating the phase deviation is: the phase deviation equals the actual arrival time minus the expected arrival time, with the result in nanoseconds. A linear conversion relationship is used when converting the phase deviation to an error voltage; the conversion formula is: the error voltage equals the proportional coefficient multiplied by the phase deviation. The specific value of the proportional coefficient is determined by the voltage-controlled sensitivity of the chaotic oscillation circuit. In this embodiment, the voltage-controlled sensitivity is 0.5 MHz per volt, and the corresponding proportional coefficient is 0.01 volts per nanosecond. For example, when the phase deviation is positive 10 nanoseconds, the error voltage is 0.1 volts; when the phase deviation is negative 10 nanoseconds, the error voltage is negative 0.1 volts.

[0085] An error voltage is applied to the varactor diode in the local chaotic oscillation circuit. The reverse bias voltage of the varactor diode has a non-linear relationship with its junction capacitance. When the error voltage changes, the capacitance of the varactor diode changes accordingly, thereby altering the instantaneous oscillation frequency of the chaotic oscillation circuit. Specifically, the error voltage passes through a low-pass filter and is then superimposed in series with the DC bias voltage of the varactor diode. The cutoff frequency of the low-pass filter is 1 kHz, used to filter out high-frequency noise. As the instantaneous oscillation frequency changes, the phase of the local chaotic oscillation circuit gradually shifts until the actual arrival time coincides with the expected arrival time. At this point, the error voltage returns to zero, completing phase alignment.

[0086] The output signal of the local chaotic oscillating loop at the current moment is used as a matching template and compared segmentally with the pre-set chaotic attractor trajectory in the encoded data packet. The chaotic attractor trajectory is obtained in advance through offline measurement: under standard conditions, the chaotic oscillating loop is driven to run for 1000 oscillation cycles, and its output voltage change curve over time is recorded. This curve is divided into 100 segments every 100 nanoseconds, and each segment is stored as a reference waveform array. The matching template is generated by taking the output voltage value of the local chaotic oscillating loop 50 nanoseconds before and after the current moment, sampling at 1 nanosecond intervals to obtain 101 discrete voltage values, which constitute the current waveform array.

[0087] The extracted waveform segments are subjected to a sliding cross-correlation operation with the theoretical waveforms corresponding to all candidate timestamps in the encoded data packet. The calculation formula for the cross-correlation operation is as follows: ;

[0088] in, The first segment of the extracted waveform Number of sampled values, total number of sampled points It equals 101; The first candidate theoretical waveform Each sample value, This is the sliding offset, with a value ranging from -10 to +10. For the cross-correlation function at the offset The values ​​at each candidate timestamp are calculated. For the theoretical waveform corresponding to each candidate timestamp, the cross-correlation function between it and the extracted waveform segment is calculated. Find the maximum value of the function. Compare the maximum cross-correlation values ​​corresponding to all candidate timestamps, and select the timestamp corresponding to the one with the largest maximum value as the expected arrival time. If the maximum values ​​corresponding to multiple candidate timestamps are equal, then take the offset. The timestamp corresponding to the one with the smallest absolute value.

[0089] To demonstrate the beneficial effects achieved in this embodiment, a ring-shaped LED display array consisting of 16 sub-regions was constructed. Each sub-region contains a chaotic oscillation loop with a nominal center frequency of 10 MHz and an initial phase randomly distributed between 0 and 360 degrees. All sub-regions are coupled through a 5-meter differential twisted-pair cable, intermittently exchanging weak coupling synchronization pulses at a frequency of 1000 times per second, with a pulse amplitude of 0.1 volts. The chaotic attractor trajectory in the encoded data packet was pre-obtained by offline measurement of 1000 oscillation cycles, and the segment length of the reference waveform array was 100 nanoseconds. The ambient temperature was controlled within a range of 25 degrees Celsius ± 1 degree Celsius, and the power supply ripple was less than 10 millivolts. During continuous operation for 60 minutes, the phase difference of the local clock reference signal of all 16 sub-regions was acquired every minute. The triangular wave output of each sub-region was simultaneously measured using an oscilloscope with a bandwidth of 2 gigahertz. Using the first sub-region as a reference, the maximum absolute deviation of the remaining 15 sub-regions relative to the reference phase was calculated. Measurement data shows that within the first 10 seconds after startup, the maximum phase deviation rapidly decreased from an initial 180 degrees to less than 5 degrees; by the first minute, the maximum phase deviation had dropped to 0.5 degrees; from the 10th to the 60th minute, the maximum phase deviation remained stable between 0.1 and 0.3 degrees, corresponding to a time deviation of 27 to 83 picoseconds. The phase deviation between the actual arrival time and the expected arrival time of all sub-regions did not exceed ±0.5 degrees within 60 minutes, and the error voltage output remained within ±0.005 volts. In contrast, using the same hardware platform but disabling chaotic synchronization pulse calibration and relying solely on the IEEE 1588 time synchronization protocol for clock alignment, after 60 minutes of operation under the same environmental conditions, the maximum phase deviation accumulated to 45 degrees, corresponding to a time deviation of 12.5 nanoseconds, resulting in a visible misalignment between adjacent sub-regions in the circular LED array. This embodiment employs a chaotic coupling synchronization method. During operation, it simulates a brief single-node disconnection scenario: the coupling channel of the 8th sub-region is interrupted for 5 seconds. After reconnection, the phase deviation of this sub-region converges from 60 degrees to below 0.3 degrees within 1.2 seconds, verifying the self-recovery capability of the chaotic system in the face of brief disconnections. The above data indicates that this embodiment can maintain the clock reference signal of the distributed sub-region at nanosecond-level alignment accuracy for a long period and is robust to electromagnetic jitter and local connection failures.

[0090] Example 6: In the phase-triggered output module, when the local clock reference signal of each sub-region reaches a preset common phase value, the decoded sub-matrix is ​​converted in parallel into current output to drive each light-emitting element, thereby completing the synchronous refresh of the entire screen. Specifically, this includes:

[0091] A voltage comparator is set up in each sub-region. The positive input of the comparator is connected to the output of the local clock reference signal, and the negative input is connected to a DC reference voltage source. The voltage value of the DC reference voltage source is equal to the instantaneous voltage amplitude corresponding to a preset common phase value. The local clock reference signal is a periodic triangular wave with a peak voltage of 5 volts and a valley voltage of 0 volts. The common phase value is set to the midpoint of the rising edge of the triangular wave, i.e., 2.5 volts. When the instantaneous amplitude of the local clock reference signal rises from below 2.5 volts to equal 2.5 volts, the voltage comparator outputs a trigger edge that transitions from a low level to a high level, with a rise time of less than 2 nanoseconds.

[0092] The trigger edge is simultaneously assigned to two paths: the first path serves directly as the start signal for the subsequent pulse width modulation circuit; the second path, after passing through an inverter, serves as the reset signal for the parallel comparator array, restoring all comparators to their initial state before each trigger edge. The repetition frequency of the trigger edge is equal to the refresh rate of the display screen. In this embodiment, the refresh rate is set to 60 Hz, meaning a trigger edge is generated every 16.67 milliseconds.

[0093] The grayscale value of each pixel in the decoded submatrix is ​​fed into a parallel comparator array driven by a local chaotic oscillating circuit. The submatrix is ​​128 rows by 64 columns, containing 8192 pixels. The grayscale value of each pixel is represented by an 8-bit binary number, ranging from 0 to 255. The parallel comparator array consists of 8192 identical voltage comparators. The positive input of each comparator is connected to the output of a digital-to-analog converter (DAC). This DAC converts the corresponding pixel grayscale value into an analog voltage threshold of 0 to 5 volts. The conversion relationship is: the threshold voltage equals the grayscale value divided by 255 and then multiplied by 5 volts.

[0094] The output signal of the local chaotic oscillation loop, after passing through a voltage divider network, generates 8192 different reference voltages. Each reference voltage is connected to the negative input of the corresponding comparator in the parallel comparator array. The voltage divider network consists of 8192 resistors of equal value connected in series, with a total resistance of 8192 kiloohms. Each resistor tap is connected to 5 volts and 0 volts respectively. A uniformly increasing reference voltage is obtained at each resistor tap, and the difference between two adjacent reference voltages is approximately 0.00061 volts (5 volts divided by 8192). The output signal of the chaotic oscillation loop drives this voltage divider network through a voltage follower, causing the reference voltage to dynamically change with the chaotic oscillation, thereby disrupting the spatial order of the comparator outputs.

[0095] A linear ramp voltage generator is activated using a trigger edge. The core of the ramp voltage generator is a circuit where a constant current source charges a capacitor. The current of the constant current source is set to 1 mA, and the capacitance is set to 1 microfarad, resulting in a charging rate of 1 volt per microsecond. When the trigger edge arrives, an analog switch short-circuits the capacitor, discharging it and bringing the ramp voltage to zero. After the trigger edge ends, the analog switch opens, and the capacitor begins linear charging, with the ramp voltage rising from 0 volts at a rate of 1 volt per microsecond. The local chaotic oscillation loop has an oscillation frequency of 10 MHz, which controls the current of the constant current source. As the oscillation frequency changes, the constant current source current adjusts proportionally, ensuring that the ramp voltage's rise rate is proportional to the oscillation frequency.

[0096] The high and low level combinations output by the parallel comparator array are compared step-by-step with the ramp voltage. Specifically, the output of each comparator is connected to the data input of a D-type flip-flop. The clock input of each D-type flip-flop is connected to the output of the ramp voltage generator, which is then shaped into a square wave signal by a Schmitt trigger. As the ramp voltage rises, it sequentially reaches the threshold voltage of each comparator, causing the corresponding comparator output to flip. This flip signal is latched by the D-type flip-flops. The outputs of all D-type flip-flops are connected to the inputs of 8192 monostable multivibrators. Each monostable multivibrator outputs a fixed-width pulse when its input transitions from low to high. The pulse width is proportional to the grayscale value of the corresponding pixel, with the scaling factor determined by the ramp voltage's rise rate. For example, a grayscale value of 255 corresponds to a pulse width of 255 microseconds, and a grayscale value of 0 corresponds to a pulse width of 0 microseconds.

[0097] The 8192 voltage pulse trains generated above are directly coupled to the anodes of each light-emitting element (LED) through a set of parallel analog switches. Each analog switch is an N-channel field-effect transistor (FET), with its gate connected to the output of the corresponding monostable multivibrator (MSF), its drain connected to the positive terminal of the DC power supply, and its source connected to the anode of the LED. The cathodes of the LEDs are grounded. When the voltage pulse train is high, the FET is turned on, and the DC power supply provides current to the LED; when the voltage pulse train is low, the FET is turned off, and the LED is extinguished. The width of each pulse precisely controls the conduction time of the LED, thereby simulating grayscale levels.

[0098] Since the trigger edges of all sub-regions originate from the moment their respective local clock reference signals reach a preset common phase value, and each sub-region has undergone chaotic synchronization calibration to align its local clock reference signals to the nanosecond level, the trigger edges of all sub-regions are physically generated simultaneously. Consequently, the start times of the voltage pulse trains corresponding to each pixel in all sub-regions are consistent. The start and end times of each light-emitting element's conduction within the pulse width are strictly synchronized, ultimately completing a full refresh of the entire screen. By repeating the above process, continuous video display can be achieved.

[0099] The working principle of this invention is as follows: First, the spatial coordinates of each sub-region and the overall pixel matrix of the image to be displayed are acquired. Then, a set of chaotic initial values ​​is assigned to each sub-region according to its spatial coordinates and injected into its chaotic oscillation circuit to generate a local clock reference signal with initial value sensitivity. Next, the overall pixel matrix is ​​decomposed into sub-matrices corresponding to each sub-region according to the spatial coordinates, and the phase of the local clock reference signal is encoded as a synchronization timestamp and embedded in the sub-matrices to form a timestamped encoded data packet. Each sub-region intermittently exchanges weak coupling synchronization pulses through a coupling channel. Utilizing the phase synchronization characteristics of the chaotic system, the phase of the chaotic oscillation circuit in this region is continuously calibrated according to the received coupling synchronization pulses and the synchronization timestamp in the local encoded data packet, so that the local clock reference signals of all sub-regions are aligned. Finally, when the local clock reference signal of each sub-region reaches a preset common phase value, the decoded sub-matrices are converted in parallel into current outputs to drive each light-emitting element, completing the synchronous refresh of the entire screen.

[0100] The foregoing has provided a detailed description of one embodiment of the present invention, but this description is merely a preferred embodiment and should not be construed as limiting the scope of the invention. All equivalent variations and modifications made within the scope of the claims of this invention should still fall within the patent coverage of this invention.

Claims

1. An LED display information matrix encoding system based on distributed control, characterized in that, include: The coordinate matrix acquisition module is used to acquire the spatial coordinates of each sub-region and the overall pixel matrix of the image to be displayed. The chaotic clock generation module assigns a set of chaotic initial values ​​to each sub-region based on spatial coordinates, and injects the chaotic initial values ​​into the local chaotic oscillation circuit of each sub-region to generate a local clock reference signal with initial value sensitivity. The submatrix encoding and packaging module decomposes the overall pixel matrix into submatrices that correspond one-to-one with each sub-region based on spatial coordinates, and encodes the phase of the local clock reference signal into a synchronization timestamp and embeds it into the submatrix to form a timestamp-encoded data packet. The pulse synchronization calibration module intermittently exchanges weak coupling synchronization pulses through the coupling channel in each sub-region. Utilizing the phase synchronization characteristics of the chaotic system, it continuously calibrates the phase of the chaotic oscillation circuit in the region based on the received coupling synchronization pulses and the synchronization timestamp in the local encoded data packet, so that the local clock reference signals of all sub-regions are aligned. The phase-triggered output module converts the decoded sub-matrix into current outputs that drive each light-emitting element in parallel when the local clock reference signal of each sub-region reaches the preset common phase value, thus completing the synchronous refresh of the entire screen.

2. The LED display information matrix encoding system based on distributed control according to claim 1, characterized in that, The process of generating the overall pixel matrix is ​​as follows: A set of chaotically encoded test light pulses is sent to each sub-region, each test light pulse carrying a unique chaotic sequence identifier; The response time series of the light-emitting elements in each sub-region to the test light pulse is collected. The response time series includes the phase difference information between the pulse arrival time and the local chaotic oscillation circuit. Based on the cross-correlation peak positions of the response time series and the chaotic sequence, the relative spatial relationships between the sub-regions are inferred, thereby reconstructing the grayscale values ​​of each pixel in the overall pixel matrix of the image to be displayed.

3. The LED display information matrix encoding system based on distributed control according to claim 1, characterized in that, The generation of a local clock reference signal with initial value sensitivity specifically includes: The three-dimensional values ​​of the spatial coordinates are used as the initial voltage of the nonlinear capacitor, the initial current of the inductor, and the bias voltage of the negative resistance element in the chaotic oscillation circuit, respectively. A transient impact pulse with a duration of one oscillation cycle is applied to the chaotic oscillation circuit, triggering the circuit to enter a chaotic oscillation state; After the impact pulse ends, the amplitude values ​​of the first three oscillation peaks of the signal output by the acquisition circuit are collected. These three amplitude values ​​are arranged in sequence to form a set of initial chaotic values, which are then locked as the basis for generating the local clock reference signal.

4. The LED display information matrix encoding system based on distributed control according to claim 3, characterized in that, The application of a transient impact pulse with a duration of one oscillation cycle to the chaotic oscillation circuit specifically includes: The output signals of the chaotic oscillation loops in two adjacent sub-regions are continuously acquired, and the instantaneous voltage difference between them is calculated. When the absolute value of the instantaneous voltage difference exceeds the preset chaotic attractor boundary threshold, a pulse generation action is triggered; Based on the current oscillation frequency of the local oscillation circuit, a complete oscillation period width is extracted as the duration of the transient impact pulse, and the transient impact pulse is injected into the local chaotic oscillation circuit.

5. The LED display information matrix encoding system based on distributed control according to claim 1, characterized in that, The process of forming a timestamped encoded data packet specifically includes: Using the spatial coordinates of each sub-region as the initial value for the chaotic mapping iteration, a set of pseudo-random permutation indices is generated after a predetermined number of iterations. The pixel grayscale values ​​at the corresponding positions are extracted from the overall pixel matrix according to the pseudo-random permutation index, and then sequentially filled into the sub-matrix of the corresponding sub-region. The current phase value of the local clock reference signal is converted into a pulse interval duration. A positioning pulse corresponding to the pulse interval duration is inserted before the starting position of the sub-matrix to form a timestamped encoded data packet.

6. The LED display information matrix encoding system based on distributed control according to claim 5, characterized in that, The step of extracting the pixel grayscale values ​​at corresponding positions from the overall pixel matrix according to the pseudo-random permutation index and sequentially filling them into the sub-matrix of the corresponding sub-region specifically includes: The current output signal voltage value of the local chaotic oscillation circuit is quantized and used as the starting decimation position; After extracting a pixel grayscale value each time, the state of the chaotic oscillation circuit is iterated once to generate the next extraction position; When the number of extracted pixel grayscale values ​​reaches the preset size of the submatrix, the final state of the chaotic oscillation circuit is saved as the initial extraction seed for the next submatrix.

7. The LED display information matrix encoding system based on distributed control according to claim 1, characterized in that, The continuous calibration of the phase of the chaotic oscillation circuit in this region, to align the local clock reference signals of all sub-regions, specifically includes: Extract the actual arrival time of the weakly coupled synchronization pulse from the received weakly coupled synchronization pulse, and at the same time, parse the expected arrival time indicated by the synchronization timestamp corresponding to the weakly coupled synchronization pulse from the local encoded data packet. Calculate the phase deviation between the actual arrival time and the expected arrival time, and convert the phase deviation into an error voltage; An error voltage is applied to the varactor diode of the chaotic oscillation circuit in this region to change the instantaneous oscillation frequency of the circuit until the actual arrival time coincides with the expected arrival time, thus completing phase alignment.

8. The LED display information matrix encoding system based on distributed control according to claim 7, characterized in that, The step of parsing the expected arrival time indicated by the synchronization timestamp corresponding to the weakly coupled synchronization pulse from the local encoded data packet specifically includes: The output signal of the local chaotic oscillation loop at the current moment is used as a matching template and compared with the pre-set chaotic attractor trajectory in the encoded data packet in segments. Each time a weak coupling synchronization pulse is received, a segment of the chaotic waveform within half an oscillation cycle before and after the arrival of the weak coupling synchronization pulse is extracted. Perform a sliding cross-correlation operation between the waveform segment and the theoretical waveform corresponding to all candidate timestamps in the encoded data packet, and select the timestamp corresponding to the cross-correlation peak position as the expected arrival time.

9. The LED display information matrix encoding system based on distributed control according to claim 1, characterized in that, The process of converting the decoded sub-matrix into parallel current outputs to drive each light-emitting element, thereby achieving synchronous refresh of the entire screen, specifically includes: The instantaneous amplitude of the local clock reference signal is compared with the reference voltage corresponding to the preset common phase value, and a trigger edge is generated when the two are equal. Based on the trigger edge, the grayscale value of each pixel in the decoded submatrix is ​​converted into a voltage pulse train of corresponding width; The voltage pulse train is directly coupled to the anode of each light-emitting element through a set of parallel analog switches, so that the light-emitting elements are turned on within the pulse width, thus completing the synchronous refresh of the entire screen.

10. The LED display information matrix encoding system based on distributed control according to claim 9, characterized in that, Based on the trigger edge, the grayscale value of each pixel in the decoded sub-matrix is ​​converted into a voltage pulse train of corresponding width, specifically including: Each pixel grayscale value in the decoded submatrix is ​​fed into a parallel comparator array driven by a local chaotic oscillation circuit. The parallel comparator array outputs a combination of high and low levels. A linear ramp voltage generator is started using the trigger edge, and the rate of rise of the ramp voltage is determined by the oscillation frequency of the local chaotic oscillation circuit. The high and low level combinations are compared with the ramp voltage step by step. When the ramp voltage reaches the threshold corresponding to each comparator, the output state is flipped, forming a voltage pulse train whose width is proportional to the gray value.

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