Miniaturized high-isolation receiving array applied to GNSS

Abstract

The application discloses a miniaturized high-isolation receiving array applied to GNSS and belongs to the technical field of antennas. The miniaturized high-isolation receiving array comprises an antenna unit and a cross-shaped electron bandgap structure, and the antenna unit is arranged in a right angle of the structure. The antenna unit is surrounded by three dielectric substrates to form a closed cuboid air cavity, a second substrate is provided with a reflecting ground, and a third substrate is covered with a bent gable-shaped metal side wall, so that left-handed or right-handed circular polarization can be realized; and a first substrate is provided with an open ring-shaped dipole arm. The cross-shaped electron bandgap structure comprises a mushroom-shaped structure, a cross-shaped metal reflecting ground and a cross-shaped dielectric block, and a top metal patch of the mushroom-shaped structure is connected with the metal reflecting ground through a metal column. The miniaturized high-isolation receiving array adopts high dielectric constant substrates to realize miniaturization, the metal side wall is connected with the reflecting ground to improve the radiation effect, the size of the dipole arm and the opening are adjusted to form circular polarization radiation, and the units are sequentially rotated to form an array and the mushroom-shaped structure is loaded to realize high isolation.

Description

Technical Field

[0001] This invention belongs to the field of antenna technology, specifically a miniaturized high-isolation receiver array for GNSS applications. Background Technology

[0002] Global Navigation Satellite Systems (GNSS), including BeiDou, GPS, and Galileo, have become indispensable technologies for modern positioning, navigation, and timing applications. With the continued growth in demand for compact, high-performance terminal devices, the development of miniaturized antenna arrays with stable radiation characteristics has received widespread attention. As terminal devices rapidly iterate towards miniaturization, integration, and high performance, scenarios such as smart wearables, automotive embedded terminals, and small drones place extremely stringent constraints on the size, weight, and power consumption (SWaP) of GNSS receiver modules. Miniaturized GNSS antenna arrays with high integration and stable radiation performance have become a current research hotspot and core focus in the field of radio frequency antennas. In GNSS receivers, circularly polarized antennas are the preferred solution due to their excellent suppression capabilities against Faraday rotation effects and multipath interference. From the perspective of GNSS signal transmission characteristics and reception requirements, circularly polarized antennas are the inevitable technical choice for GNSS receivers: First, when GNSS signals pass through the ionosphere, the polarization plane deflects due to the Faraday rotation effect. Linearly polarized antennas will experience significant fluctuations in received power due to polarization mismatch, and may even experience signal loss. Circularly polarized antennas, however, are unaffected by polarization plane rotation, achieving stable reception of satellite signals. Second, in complex environments with significant multipath effects, such as urban canyons, indoor spaces, and vehicle-mounted environments, reflected signals will undergo polarization twisting. Circularly polarized antennas have a natural and strong suppression capability against cross-polarization components, which can significantly reduce positioning errors caused by multipath interference and ensure positioning accuracy and stability. Third, for the design requirements of multi-frequency and multi-system compatibility, wide-beam, wide-axis-ratio bandwidth circularly polarized antennas can simultaneously cover multiple GNSS operating frequency bands, meeting the requirements for full constellation signal reception.

[0003] Compared to traditional single-element antennas, multi-element antenna arrays can achieve beamforming, interference nulling, incoming wave direction estimation, and carrier attitude measurement through spatial signal processing. This can significantly improve the receiver's anti-interference capability and weak signal acquisition and tracking performance in complex electromagnetic environments, and is the core hardware foundation of high-performance anti-interference GNSS receivers.

[0004] Under the stringent constraints of miniaturization, the design of GNSS antenna arrays faces a core inherent contradiction: to ensure the array's anti-interference and beamforming performance, it is necessary to ensure that the array elements have consistent amplitude and phase characteristics and stable radiation performance; however, to meet the compact size requirements of the terminal, the spacing between array elements needs to be much smaller than the half-wavelength critical value of traditional array design (the free space half-wavelength of the GNSS L1 band is about 75mm), or even compressed to 1 / 4 wavelength or less. At this time, the electromagnetic mutual coupling effect between adjacent array elements will be sharply enhanced, becoming a bottleneck restricting the array performance.

[0005] Specifically, the mutual coupling effect between array elements originates from the spatial electromagnetic field coupling and surface current coupling of adjacent array elements. Its negative impact on array performance covers multiple core dimensions, ultimately directly degrading the overall receiver performance: Impedance matching performance deterioration: Mutual coupling effect will disturb the near-field distribution of array elements, causing a significant shift in the input impedance of array elements, destroying the original impedance matching design, resulting in reduced return loss and increased VSWR of the antenna, a significant decrease in receiving efficiency within the operating bandwidth, and even some frequency band mismatch, which cannot meet the broadband coverage requirements of multi-frequency and multi-system. Deterioration of axial ratio characteristics of circular polarization: The core performance of circular polarization antennas depends on the equal amplitude radiation of two orthogonal polarization modes and a 90° phase difference. However, the mutual coupling effect will break the amplitude and phase balance of the orthogonal modes, resulting in a significant increase in the axial ratio of the antenna and a sharp decrease in the purity of circular polarization. This directly leads to the loss of the ability to suppress Faraday rotation effect and multipath interference, ultimately causing a decrease in receiver positioning accuracy and signal tracking instability. Impaired radiation pattern stability: Mutual coupling effect can cause distortion of the radiation pattern of array elements, resulting in problems such as main beam shift, side lobe level rise, front-to-back ratio deterioration, and even beam splitting. This disrupts the amplitude and phase consistency of each array element, making it impossible to achieve the preset beamforming and interference nullification effect, and significantly reducing the array's anti-interference performance and direction finding accuracy. Overall system performance degradation: The deterioration of the above-mentioned core indicators will directly affect the GNSS receiver as a whole, resulting in decreased receiver sensitivity, insufficient anti-interference capability, and weakened multipath suppression capability. In complex environments, it will be unable to achieve stable high-precision positioning and will not be able to meet the application requirements of compact high-performance terminals.

[0006] To address the mutual coupling suppression problem in compact array antennas, existing mainstream technologies include defective ground structures, neutral lines, decoupling resonant units, and metasurface coverings. However, these solutions all have significant limitations in the miniaturized design of GNSS circularly polarized arrays: defective ground structures disrupt the integrity of the antenna floor, leading to increased cross-polarization levels and further deteriorating the axial ratio performance of circular polarization; neutral lines and decoupling resonant units have narrow effective operating bandwidths, making it difficult to meet the wideband design requirements of multi-frequency, multi-system GNSS antennas; and metasurface decoupling solutions significantly increase the antenna profile height and design and manufacturing complexity, failing to meet the requirements of low profile, miniaturization, and low cost for compact terminals.

[0007] In summary, achieving high isolation between elements of a GNSS circularly polarized array under extremely compact size constraints, while simultaneously ensuring wide axial ratio bandwidth, good impedance matching, and stable radiation performance, remains a key technical problem that urgently needs to be solved in the field of GNSS antennas. Summary of the Invention

[0008] To address the problems existing in the prior art, this invention provides a miniaturized high-isolation receiver array for GNSS, which solves the problem that mutual coupling between adjacent array elements leads to decreased impedance matching performance, deterioration of axial ratio characteristics, and damage to radiation pattern stability.

[0009] To achieve the above objectives, the present invention provides a miniaturized high-isolation receiver array for GNSS applications, comprising an antenna element and a cross-shaped electronic bandgap structure. The antenna element is disposed within the right angle of the cross-shaped electronic bandgap structure. The antenna element includes a first dielectric substrate, a second dielectric substrate, a third dielectric substrate, a reflective ground, and an open-ended annular dipole arm. The first, second, and third dielectric substrates form a closed cuboid air cavity. The first and second dielectric substrates are the top and bottom surfaces of the cuboid, respectively, and the third dielectric substrate is the side surface of the cuboid. The reflective ground is located on the outer surface of the second dielectric substrate. The outer surface of the third dielectric substrate is covered with a bent grid-like metal sidewall, which is used to achieve left-hand circular polarization or right-hand circular polarization. The open-ended annular dipole arm is disposed on two surfaces of the first dielectric substrate. The cross-shaped electronic bandgap structure includes several mushroom-shaped structures, a complete cross-shaped metal reflective ground, and a cross-shaped dielectric block. The top of the mushroom-shaped structure is a square metal patch, and a metal pillar is disposed through the cross-shaped dielectric block to connect the cross-shaped metal reflective ground and the square metal patch.

[0010] Furthermore, the bent grid-like metal sidewall includes multiple evenly spaced metal strips, each metal strip having a bending angle, with the bending angle of each metal strip facing the same direction.

[0011] Furthermore, the open-ended annular dipole arm includes a first dipole arm and a second dipole arm. The first dipole arm is disposed on the outer surface of the first dielectric substrate, and the second dipole arm is disposed on the inner surface of the first dielectric substrate. The first dipole arm includes a first annular structure and a second annular structure. The first annular structure is located on the outer ring of the second annular structure. The first annular structure has an opening of a predetermined width. The outer ring of the second annular structure has a continuous quarter ring removed. A first circular patch is disposed at the center of the second annular structure. The first circular patch is connected to one end of the second annular structure through a first metal strip. The other end of the second annular structure is connected to the first end of the opening of the first annular structure through a second metal strip. The shape of the second dipole arm is obtained by rotating the first dipole arm 180° around its own center. The second dipole arm has a different size from the first dipole arm.

[0012] Furthermore, the first metal strip is perpendicular to the second metal strip, and the first end is located on one side of the first metal strip.

[0013] Furthermore, the first metal strip and the second metal strip have the same width.

[0014] Furthermore, the azimuth angle difference of each antenna element is 90°.

[0015] Furthermore, in the cross-shaped electronic bandgap structure, the square metal patch is located on the top surface of the cross-shaped dielectric block, and the mushroom-shaped structure is evenly distributed in four directions with the center of the cross as the origin.

[0016] Furthermore, the dielectric constant of the materials of the first dielectric substrate, the second dielectric substrate, and the third dielectric substrate is 10.9, and the loss tangent is 0.0023.

[0017] Furthermore, the antenna element adopts a 50-ohm coaxial feed, the inner conductor is connected to the reflective ground and the open ring dipole arm on the outer surface of the first dielectric substrate, and the outer conductor is connected to the open ring dipole arm on the inner surface of the first dielectric substrate.

[0018] The present invention can also provide a GNSS receiver, including the miniaturized high-isolation receiving array for GNSS described above.

[0019] Compared with the prior art, the present invention has the following beneficial technical effects: This invention provides a miniaturized, high-isolation receiver array for GNSS applications, wherein the antenna element includes a pair of open-loop annular dipole arms, a complete reflective ground plane, and bent metal sidewalls on all four sides. The element is fed via a 50-ohm coaxial line. To achieve miniaturization, a high-dielectric-constant material is selected as the dielectric substrate. The asymmetric open-loop annular dipole arms are printed on the upper and lower surfaces of the first dielectric substrate, respectively. The specific dipole structure includes an open ring, a three-quarter ring connected to the inner and outer conductors of the coaxial line, and a metal strip connecting the two. The far-field electric fields generated by the current on the open-loop annular dipole arms are superimposed or canceled, causing the far-field electric field direction of the antenna to rotate counterclockwise or clockwise, corresponding to right-hand circular polarization or left-hand circular polarization. The bent metal sidewalls on all four sides are directly connected to the complete reflective ground plane below, ensuring good radiation while miniaturizing. Furthermore, to ensure high isolation within a compact size, the antenna elements are rotated sequentially, and a mushroom-shaped electronic bandgap decoupling structure is placed between the elements. Attached Figure Description

[0020] Figure 1 This is a schematic diagram of the antenna unit structure of the present invention; Figure 2 These are three views of the antenna unit structure of the present invention; Figure 3 This is a schematic diagram of the open-ring dipole arm structure in the antenna unit of the present invention; Figure 4 This is a schematic diagram of the 2×2 array structure of the present invention; Figure 5 These are three structural views of the 2×2 array of the present invention; Figure 6 This is a schematic diagram of the return loss of the antenna element of the present invention; Figure 7 This is the two-dimensional radiation pattern of the antenna element of the present invention (Phi=0°, F=1.268GHz). Figure 8 This is the two-dimensional radiation pattern of the antenna element of the present invention (Phi=45°, F=1.268GHz). Figure 9 This is the two-dimensional radiation pattern of the antenna element of the present invention (Phi=90°, F=1.268GHz). Figure 10 This is a schematic diagram showing the change of the normal axis ratio of the antenna element of the present invention with frequency; Figure 11 This is a schematic diagram of the S-parameters of the 2×2 array of the present invention (S11). Figure 12 This is a schematic diagram of the S-parameters of the 2×2 array of the present invention (S21); Figure 13 This is a schematic diagram of the S-parameters of the 2×2 array of the present invention (S31); Figure 14 This is a schematic diagram of the S-parameters of the 2×2 array of the present invention (S41). Figure 15 This is a schematic diagram of the active VSWR of the 2×2 array of the present invention (port 1). Figure 16 This is the two-dimensional radiation pattern of the 2×2 array of the present invention (Phi=0°, F=1.268GHz). Figure 17 This is the two-dimensional radiation pattern of the 2×2 array of the present invention (Phi=45°, F=1.268GHz). Figure 18 This is the two-dimensional radiation pattern of the 2×2 array of the present invention (Phi=90°, F=1.268GHz).

[0021] In the attached diagram, 1-antenna element, 2-cross-shaped electronic bandgap structure, 11-first dielectric substrate, 12-second dielectric substrate, 13-third dielectric substrate, 14-reflective ground, 15-bent grid-shaped metal sidewall, 16-first dipole arm, 17-second dipole arm, 21-mushroom-shaped structure, 22-cross-shaped metal reflective ground, 23-cross-shaped dielectric block, 24-square metal patch, 25-metal pillar. Detailed Implementation

[0022] The present invention will now be described in further detail with reference to the accompanying drawings. These descriptions are intended to explain the invention and not to limit it.

[0023] See Figure 1 , Figure 2 , Figure 3 , Figure 4 and Figure 5 This application provides a miniaturized high-isolation receiver array for GNSS, including an antenna element and a cross-shaped electronic bandgap structure; The antenna element includes a dielectric substrate, a reflective ground, a bent grid-like metal sidewall, and an open annular dipole arm.

[0024] Furthermore, the dielectric substrate includes a first dielectric substrate 11 (with dimensions of L×L×TH), a second dielectric substrate 12 (with dimensions of L×L×TH), and a third dielectric substrate 13 (with dimensions of H×L×TH). The first dielectric substrate 11, the second dielectric substrate 12, and the third dielectric substrate 13 together form a closed cuboid air cavity. The outer surface of the first dielectric substrate 11 faces the outside of the cuboid air cavity, and the inner surface of the first dielectric substrate 11 is located inside the cuboid air cavity.

[0025] Furthermore, the reflective ground surface 14 is located on the outer surface of the second dielectric substrate 12.

[0026] Furthermore, Figure 2In the diagram, a is a top view of the antenna element, b is a front view of the antenna element, c is a side view of the antenna element, and d is a three-dimensional view of the antenna element. The bent grid-like metal sidewall 15 is formed through the following process: First, a series of identical metal strips (H1×W) are uniformly placed on a rectangular surface (H×4L), with a strip spacing of D; then, the portion of the metal strip above the height H2 (H2

[0027] Figure 3 In the diagram, a is a schematic diagram of the first dipole arm 16, and b is a schematic diagram of the second dipole arm 17. Further, the open annular dipole arms are respectively printed on the outer and inner surfaces of the first dielectric substrate 11, with the first dipole arm 16 printed on the outer surface and the second dipole arm 17 printed on the inner surface. Taking right-hand circular polarization as an example... Figure 2 The first dipole arm 16 is formed as shown in Figure a, which describes the orientation as follows: First, a first annular structure (inner diameter 2×R1, ring width W1) is made, followed by a second annular structure (inner diameter 2×R2, ring width W2). Then, the upper right quarter ring of the second annular structure is cut off, leaving only the remaining three-quarter ring. Next, a first circular patch (radius R3) is placed at the center of the ring, and a first metal strip with a width of W3 connects the first circular patch to the upper part of the three-quarter ring with a first metal strip of the same width W3. A second metal strip of the same width W3 connects the right side of the three-quarter ring of the second annular structure to the first annular structure, and a notch with a width of W4 is made on the first annular structure from the junction downwards, so that the overall structure is a counterclockwise right-hand spiral (viewed from the top to the bottom). The first metal strip is perpendicular to the second metal strip.

[0028] The second dipole arm 17 is formed through the following process: Figure 3 ​In the diagram (b), the orientation is described as follows: First, construct the third circular structure, with an inner diameter of 2×R4 and a width of W5. Then, construct the fourth circular structure, with an inner diameter of 2×R5 and a width of W6. Next, cut off the lower left quarter of the fourth circular structure, leaving only the remaining three-quarters of the circular structure. Immediately afterward, place the second circular patch (radius R6) at the center of the circular structure and connect it to the lower part of the three-quarters of the circular structure with a third metal strip of width W7. Connect the left side of the three-quarters of the fourth circular structure to the third circular structure with a fourth metal strip of the same width W7. From the point of connection, create a notch of width W8 on the third circular structure, making the overall structure a counterclockwise right-handed spiral (viewed from the top to the bottom). The third and fourth metal strips are perpendicular to each other.

[0029] Taking left-handed circular polarization as an example, the first dipole arm 16 is formed through the following process: First, a first circular ring structure (inner diameter 2×R1, ring width W1) is made, and then a second circular ring structure (inner diameter 2×R2, ring width W2) is made; then, the upper left quarter ring of the second circular ring structure is cut off, leaving only the remaining three-quarter ring; then, a first circular patch (radius R3) is placed at the center of the ring, and a first metal strip with a width of W3 is used to connect it to the top of the three-quarter ring; then, a second metal strip with the same width of W3 is used to connect the left side of the three-quarter second circular ring structure to the first circular ring structure, and a notch with a width of W4 is made on the first circular ring structure from the junction downwards, so that the overall structure is a clockwise left-handed spiral (viewed from the top to the bottom). The second dipole arm 17 is formed through the following process: First, a third annular structure (inner diameter 2×R4, ring width W5) is made, then a fourth annular structure (inner diameter 2×R5, ring width W6) is made; then, the lower right quarter of the fourth annular structure is cut off, leaving only the remaining three-quarters of the annular structure; then, a second circular patch (radius R6) is placed at the center of the ring, and a third metal strip with a width of W7 is used to connect it to the lower part of the three-quarters of the fourth annular structure; then, a fourth metal strip with the same width of W7 is used to connect the right side of the three-quarters of the fourth annular structure to the third annular structure, and a notch with a width of W8 is made on the third annular structure from the connection point upwards, so that the overall structure is in the shape of a clockwise left-handed spiral (viewed from the top to the bottom).

[0030] Furthermore, the antenna element adopts a 50-ohm coaxial feed, with the probe being the inner conductor. During feeding, the probe is connected to the first circular patch at the center of the first dipole arm 16, and the outer conductor is connected to the second circular patch of the second dipole arm 17.

[0031] Figure 5In the diagram, a is a top view of the miniaturized high-isolation GNSS receiver array, b is a front view of the miniaturized high-isolation GNSS receiver array, c is a side view of the miniaturized high-isolation GNSS receiver array, and d is a three-dimensional view of the miniaturized high-isolation GNSS receiver array. The cross-shaped electronic bandgap structure 2 includes several mushroom-shaped structures 21, a complete cross-shaped metal reflective ground 22, and a cross-shaped dielectric block 23. Each mushroom-shaped structure includes a square metal patch 14 and a metal pillar 25 (with a base radius of R0 and a height of H0). The side length of the square metal patch 24 is W0, and the base radius of the metal pillar 25 is R0 and the height is H0. The square metal patch 24 is located on the top surface of the cross-shaped dielectric block 23. The metal pillar 25 connects the square metal patch 24 on the top surface and the cross-shaped metal reflective ground 22 on the bottom surface by penetrating the entire cross-shaped dielectric block 23. All the mushroom-shaped structures 21 are evenly distributed in four directions with the center of the cross as the origin, and the distribution spacing is D0. Considering that the envelope size of the array is Lmax×Lmax, the cross metal reflective ground 22 can be regarded as the integration of two mutually orthogonal rectangles, where the size of the rectangle is (Lmax-2×L)×Lmax; similarly, the cross dielectric block 23 can also be regarded as the integration of two mutually orthogonal cuboids, where the size of the cuboid is (Lmax-2×L)×Lmax×H0.

[0032] Furthermore, the array is formed by the following process: rotating the antenna elements 1 obtained above sequentially by 90 degrees, and ensuring that the spacing between the antenna elements 1 is Lmax-2×L; then placing the cross-shaped electronic bandgap structure 2 obtained above in the middle of the elements.

[0033] Example 1 A miniaturized, high-isolation receiver array for GNSS applications is proposed. First, Rogers 6010 dielectric substrate is selected, with a dielectric constant of 10.9 and a loss tangent of 0.0023. Then, suitable parameter values ​​are chosen to construct the envisioned array structure.

[0034] See Figure 6-10 The following results were obtained by simulating the performance parameters of the antenna element using Ansys electromagnetic simulation software: (Reference) Figure 6 As can be seen, the antenna element operates in the 1.24-1.3 GHz frequency range, with a relative bandwidth of 4.7%; (Reference) Figure 7 , Figure 8 and Figure 9 As can be seen, this antenna element exhibits good right-hand circular polarization radiation capability at the center frequency, and the antenna gain at the center frequency is approximately 3.0 dBi; (Reference) Figure 10 As can be seen, the 3dB axial ratio bandwidth of this antenna element is approximately 20MHz.

[0035] See Figure 11-18 The following results were obtained by simulating a 2×2 array using Ansys electromagnetic simulation software. Considering the structural symmetry, only the self-reflection coefficient of one element and the mutual coupling coefficient of that antenna element to the other three antenna elements are given: Reference Figure 11 It can be seen that the self-reflection coefficient of this antenna element is less than -10dB within a given bandwidth; Reference Figure 12 , Figure 13 and Figure 14 It can be seen that within a given bandwidth, the mutual coupling coefficient of this antenna element to the other three antenna elements is less than -15dB; Reference Figure 15 As can be seen, when four antenna elements are excited simultaneously, the active VSWR of this antenna element is less than 2 within a given bandwidth; Reference Figure 16 , Figure 17 and Figure 18 As can be seen, under sequential rotating feed conditions, the array has good right-hand circular polarization radiation capability at the center frequency, and the array gain at the center frequency is about 5.9 dBi.

[0036] This invention provides a miniaturized, high-isolation receiver array for GNSS applications, wherein the antenna element includes a dielectric substrate, a complete reflective ground plane, bent grid-like metal sidewalls, and a pair of asymmetrical open annular dipole arms. The dielectric substrate is made of a material with a high dielectric constant to achieve miniaturization, and the metal sidewalls are connected to the reflective ground plane to ensure good electromagnetic radiation. By adjusting the size of the upper and lower dipole arms and the size of the opening, the far-field electric fields generated by the current on the arms are coherently interfered, achieving rotation of the electric field direction to achieve circularly polarized radiation. The antenna elements are sequentially rotated and arrayed, and a mushroom-shaped electronic bandgap structure is loaded between the elements to achieve high isolation.

[0037] The above content is only for illustrating the technical concept of the present invention and should not be construed as limiting the scope of protection of the present invention. Any modifications made to the technical solution based on the technical concept proposed in this invention shall fall within the scope of protection of the claims of this invention.

Claims

1. A miniaturized, high-isolation receiver array for GNSS applications, characterized in that, The antenna unit (1) includes an antenna element (1) and a cross-shaped electronic bandgap structure (2). The antenna element (1) is located in the right angle of the cross-shaped electronic bandgap structure (2). The antenna element (1) includes a first dielectric substrate (11), a second dielectric substrate (12), a third dielectric substrate (13), a reflective ground (14), and an open annular dipole arm. The first dielectric substrate (11), the second dielectric substrate (12), and the third dielectric substrate (13) form a closed cuboid air cavity. The first dielectric substrate (11) and the second dielectric substrate (12) are the top and bottom surfaces of the cuboid, respectively. The third dielectric substrate (13) is the side surface of the cuboid. The reflective ground (14) is located on the outer surface of the second dielectric substrate (12). The outer surface (13) of the third dielectric substrate is covered with a bent grid-shaped metal sidewall (15), which is used to realize left-hand circular polarization or right-hand circular polarization; the open annular dipole arm is set on the two surfaces of the first dielectric substrate; the cross electronic bandgap structure (2) includes several mushroom-shaped structures (21), a complete cross metal reflective ground (22) and a cross dielectric block (23). The top of the mushroom-shaped structure (21) is a square metal patch (24), and a metal pillar (25) is set to pass through the cross dielectric block (23) to connect the cross metal reflective ground (22) and the square metal patch (24).

2. The miniaturized high-isolation receiver array for GNSS according to claim 1, characterized in that, The bent grid-like metal sidewall (15) includes multiple evenly spaced metal strips, each metal strip having a bend angle, and the bend angles of each metal strip are aligned in the same direction.

3. A miniaturized high-isolation receiver array for GNSS according to claim 1, characterized in that, The open-ring dipole arm includes a first dipole arm (16) and a second dipole arm (17). The first dipole arm (16) is disposed on the outer surface of the first dielectric substrate (11), and the second dipole arm (17) is disposed on the inner surface of the first dielectric substrate (11). The first dipole arm (16) includes a first ring structure and a second ring structure. The first ring structure is located on the outer ring of the second ring structure. The first ring structure has an opening of a set width. The outer ring of the second ring structure has a continuous quarter ring removed. A first circular patch is disposed at the center of the second ring structure. The first circular patch is connected to one end of the second ring structure through a first metal strip. The other end of the second ring structure is connected to the first end of the opening of the first ring structure through a second metal strip. The shape of the second dipole arm is obtained by rotating the first dipole arm 180° around its own center. The second dipole arm has a different size from the first dipole arm.

4. A miniaturized high-isolation receiver array for GNSS according to claim 3, characterized in that, The first metal strip is perpendicular to the second metal strip, and the first end is located on one side of the first metal strip.

5. A miniaturized high-isolation receiver array for GNSS according to claim 3, characterized in that, The first metal strip and the second metal strip have the same width.

6. A miniaturized high-isolation receiver array for GNSS according to claim 1, characterized in that, The azimuth angle difference of each antenna element is 90°.

7. A miniaturized high-isolation receiver array for GNSS according to claim 1, characterized in that, In the cross-shaped electronic bandgap structure, the square metal patch is located on the top surface of the cross-shaped dielectric block, and the mushroom-shaped structure is evenly distributed in four directions with the center of the cross as the origin.

8. A miniaturized high-isolation receiver array for GNSS according to claim 1, characterized in that, The dielectric constant of the first dielectric substrate, the second dielectric substrate, and the third dielectric substrate is 10.9, and the loss tangent is 0.0023.

9. A miniaturized high-isolation receiver array for GNSS according to claim 1, characterized in that, The antenna element is fed by a 50-ohm coaxial power supply. The inner conductor is connected to the reflective ground and the open ring dipole arm on the outer surface of the first dielectric substrate. The outer conductor is connected to the open ring dipole arm on the inner surface of the first dielectric substrate.

10. A GNSS receiver, characterized in that, Including a miniaturized, high-isolation receiver array for GNSS as described in any one of claims 1 to 9.

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