Dual-polarized directional standing wave waveguide antenna and its downtilt angle design method

Abstract

The application discloses a dual-polarized directional standing wave leaky-wave antenna and a design method of a downward inclination angle thereof, and the antenna comprises, from top to bottom, a metal strip layer, a first dielectric layer, a first metal ground and an artificial magnetic conductor reflector plate, the metal strip layer comprises two metal strips which are symmetrically distributed along a central axis in a y direction of the first dielectric layer, the metal strip comprises a matching transition structure on both sides of a center feed and an artificial surface plasmon structure with different slot depths, the first metal ground is etched with periodic composite slots, and the slot periods on both sides of the center feed are different; the artificial magnetic conductor reflector plate is separated from the first metal ground by an air layer; the dual-polarized leaky-wave radiation is realized through period control of the composite slots; in addition, the downward inclination angle can be designed by reasonably designing the slot depths of the artificial surface plasmon structures on both sides of the feed and the slot periods of the first metal ground; and the application is suitable for large-aperture high-gain long-distance mobile communication.

Description

Technical Field

[0001] This invention belongs to the field of base station antennas, and particularly relates to a dual-polarized directional standing wave leaky wave antenna and a downtilt design method. Background Technology

[0002] Base station antennas are information-energy converters between base station equipment and end users, acting as intermediaries for transmitting and receiving signals. The performance of base station antennas directly affects the quality of mobile communication. Current base station antenna products, in order to achieve high-gain radiation, generally employ multi-array parallel-fed base station antenna arrays. Since each resonant antenna requires individual feeding, this results in a large number of feed lines, high electromagnetic wave transmission loss, and the need for multi-layer designs, leading to a high antenna profile and high cost. Therefore, there is significant room for improvement. The fundamental way to reduce feed line loss is to reduce the amount of feed lines used. Leaky wave antennas, being waveguide structures, do not require power divider feed networks; using them as array elements can significantly reduce the amount of feed lines required.

[0003] However, traditional traveling-wave leaky-wave antennas possess inherent beam frequency scanning characteristics due to waveguide dispersion. While this is advantageous in certain applications, for point-to-point communication, directional radiation within a specific bandwidth is often required. Therefore, to overcome this issue, center-fed standing-wave leaky-wave antennas have been proposed. By combining two leaky waves with opposite directions, wide-side radiation can be achieved within a certain frequency range.

[0004] However, in practical applications of base station antennas, it is often necessary to... Dual polarization enhances communication capacity and stability, while a suitable downtilt angle allows for precise control of coverage and suppression of interference at distant locations, thus improving overall communication quality. However, currently reported standing wave leaky wave antennas can only achieve single polarization and wide-side radiation.

[0005] According to existing technology, there are no reports of standing wave leaky wave antennas that can achieve dual polarization and downtilt radiation characteristics. Summary of the Invention

[0006] Purpose of the invention: The purpose of this invention is to provide a dual-polarized directional standing wave leaky wave antenna with low profile characteristics and its downtilt angle design method.

[0007] Technical Solution: The antenna of the present invention includes: a metal strip layer, a first dielectric layer, a first metal ground, and an artificial magnetic conductor reflector. The metal strip layer is located on the upper surface of the first dielectric layer and includes two metal strips symmetrically distributed along the central axis of the first dielectric layer in the y-direction. Each metal strip includes a matching transition structure and an artificial surface plasmon structure with open ends. The slot depths of the artificial surface plasmon structures on both sides of the feed center are different. The first metal ground is etched with periodic composite slots. The distances from the feed center to the composite slots on both sides are different, and the slot periods on both sides of the feed center are different. An air layer separates the first metal ground and the artificial magnetic conductor reflector. The radio frequency signal sequentially passes through the vias of the artificial magnetic conductor reflector and the vias of the first metal ground and the first dielectric layer to connect with the feed centers of the two metal strips. After passing through the matching transition structures on both sides, the signal is fed into the artificial surface plasmon structures on both sides.

[0008] Optionally, the composite gap of the first metal ground includes a transverse gap and a longitudinal gap, with the centers of the longitudinal gap and the transverse gap connected.

[0009] Optionally, the distance from the power supply center to the first lateral gap on each side can be different.

[0010] Optionally, the artificial magnetic conductor reflector comprises, from top to bottom, an array layer of periodic artificial magnetic conductor units, a second dielectric layer, and a second metal ground.

[0011] Optionally, the periodic unit of the artificial magnetic conductor is a square patch, and the size of the square patch and the period of the unit meet the reflection phase requirements in the operating frequency band.

[0012] The antenna downtilt design method of the present invention includes: by designing the slot depth of the plasmonic structure on the artificial surface on both sides of the feed center and the slot period of the first metal ground, the propagation constant on both sides is controlled to form an equivalent tilted equiphase surface, and a standing wave leakage wave with edge reflection effect is directionally radiated within a preset frequency band.

[0013] Furthermore, the method for adjusting the propagation constants on both sides is as follows: the normalized far-field radiation pattern is calculated based on the expression for the directional coefficient, and the theoretical downtilt angle is read from the pattern; if the deviation between the theoretical angle and the expected angle is too large, the propagation constants on both sides are adjusted and substituted into the expression again, and the new theoretical downtilt angle is obtained through further calculation until the error between the theoretical angle and the expected angle meets the requirements; under the guidance of the propagation constants on both sides required by the theory at the obtained expected radiation angle, the slot depth of the plasmonic structure on the artificial surface on both sides of the feed center and the slotting period of the first metal ground are designed so that the resulting propagation constant is consistent with the theory;

[0014] The expression for the directionality coefficient is:

[0015] ;

[0016] in, Indicates the directional coefficient. Indicates in Far-field pattern function in the direction, Represents the angle of the integral variable. Represents the far-field pattern function. Indicates the angle between the observation direction and the direction of the antenna normal;

[0017] ;

[0018] in, Indicates the overall aperture field distribution. This indicates the displacement relative to the feeder. Indicates the length from the feed to one end of the antenna. and Let these represent the propagation constants on both sides. and They represent going to and The amplitude of the propagating reflected wave, It is the propagation constant of electromagnetic waves in free space.

[0019] An electronic device, comprising:

[0020] Memory, used to store computer programs;

[0021] A processor for executing the computer program to implement the method.

[0022] A non-volatile storage medium for storing a computer program, wherein the computer program implements the method when executed by a processor.

[0023] A computer program product includes a computer program / instructions that, when executed by a processor, implement the method described.

[0024] Beneficial Effects: Compared with the prior art, the significant technical effects of this invention are as follows: The dual-polarized directional standing wave leaky antenna of this invention etches a combination of transverse and longitudinal slots onto the first metal ground, enabling fast-wave leaky radiation through slow-wave periodic modulation; by rationally designing the distance from the feed center to the first transverse slots on both sides, while achieving co-polarized radiation on both sides of the feed, because the two metal strips are symmetrically distributed along the central axis, the electric field distribution in the longitudinal slot is opposite when different ports are excited. This, combined with the co-polarized electric field in the transverse slots, cleverly achieves... Dual polarization; This invention, by designing the slot depth of the plasmonic structures on both sides of the center feed and the slot period of the first metal ground, controls the propagation constant on both sides to effectively form an inclined equiphase surface, thereby achieving directional radiation with a downtilt angle within a certain operating bandwidth; To improve the radiation gain of the upper half-space, this invention uses an artificial magnetic conductor reflector, thereby reducing the antenna profile; Therefore, this invention extends the radiation performance of the standing wave leaky wave antenna to a certain extent and overcomes the problems of large feed line usage and loss in traditional array antennas. It can be used as the basic unit of a large-aperture high-gain base station array antenna and has important practical application value in point-to-point long-distance communication. Attached Figure Description

[0025] Figure 1 This is a schematic diagram of the overall structure of the dual-polarized directional standing wave leaky antenna of the present invention;

[0026] Figure 2 This is a schematic diagram of the first dielectric layer and its upper surface structure;

[0027] Figure 3 This is a schematic diagram of the first metallic ground structure on the lower surface of the first dielectric layer;

[0028] Figure 4 This is a schematic diagram of the upper surface structure of an artificial magnetic conductor reflector.

[0029] Figure 5 This is a schematic diagram of the periodic structure of the slotting control on the left and right sides of the power supply of the present invention, wherein (a) is a periodic unit of the composite slotting on the left side of the power supply, and (b) is a periodic unit of the composite slotting on the right side of the power supply.

[0030] Figure 6 This is a schematic diagram of the artificial surface plasmon unit structure and the dark dispersion curves of different grooves of the present invention;

[0031] Figure 7 This is a schematic diagram of the directional standing wave leakage radiation principle model of the present invention;

[0032] Figure 8 The diagram shows the model verification results of the present invention, where (a) is the curve of the normalized phase constant and attenuation constant obtained from the near field extraction calculation of the present invention as a function of frequency; (b) is a comparison of the normalized far field radiation pattern obtained by theoretical calculation and simulation of the present invention at 3.5 GHz.

[0033] Figure 9 This is a vector distribution diagram of the electric field near the 3.4GHz center feed under different port excitations of the present invention; where (a) is port 1 and (b) is port 2;

[0034] Figure 10 This invention relates to the periodic square unit structure of an artificial magnetic conductor and its reflection phase curve;

[0035] Figure 11 This is a processing diagram of the present invention, wherein (a) is the upper surface of the first dielectric layer, (b) is the lower surface of the first dielectric layer, (c) is the upper surface of the artificial magnetic conductor reflector, and (d) is an overall effect diagram after assembly.

[0036] Figure 12 This is a comparison chart of the S-parameters of the simulation and test of the present invention, where (a) are the reflection coefficients S11 and S22, and (b) are the isolation coefficients S21 and S12;

[0037] Figure 13 This is a comparison of the simulation and test far-field radiation patterns of the present invention, wherein (a) is the simulation and test far-field radiation pattern with polarization of -45° under port 1 excitation at 3.4 GHz, (b) is the simulation and test far-field radiation pattern with polarization of -45° under port 1 excitation at 3.5 GHz, (c) is the simulation and test far-field radiation pattern with polarization of -45° under port 1 excitation at 3.6 GHz, (d) is the simulation and test far-field radiation pattern with polarization of 45° under port 2 excitation at 3.4 GHz, (e) is the simulation and test far-field radiation pattern with polarization of 45° under port 2 excitation at 3.5 GHz, and (f) is the simulation and test far-field radiation pattern with polarization of 45° under port 2 excitation at 3.6 GHz.

[0038] In the figure: 1. First dielectric layer; 2. Artificial magnetic conductor reflector; 3. SMA connector; 11. Matching transition structure; 12. Artificial surface plasmon structure; 13. First metal ground; 21. Artificial magnetic conductor periodic square cell array layer; 22. Second dielectric layer; 23. Second metal ground. Detailed Implementation

[0039] The present invention will be further described below with reference to the accompanying drawings and specific embodiments.

[0040] To better understand the purpose, structure, and function of this invention, the following detailed description of the dual-polarized directional standing wave leaky wave antenna and its downtilt design method is provided in conjunction with the accompanying drawings.

[0041] like Figures 1 to 4As shown, the dual-polarized directional standing wave leaky antenna of the present invention comprises, from top to bottom: a metal strip layer, a first dielectric layer 1, a first metal ground 13, and an artificial magnetic conductor reflector 2. The artificial magnetic conductor reflector comprises, from top to bottom: an artificial magnetic conductor periodic unit array layer 21, a second dielectric layer 22, and a second metal ground 23. The metal strip layer includes two metal strips located on the upper surface of the first dielectric layer, including a matching transition structure 11 and artificial surface plasmon structures 12 on both sides. The two metal strips are aligned with the central axis of the first dielectric layer along the y-direction. The distribution is as follows: a first metal ground covers the lower surface of the first dielectric layer, and the first metal ground is etched with periodic gaps. Each modulation cycle contains a set of composite gaps in which transverse gaps and longitudinal gaps are connected, and the centers of the longitudinal gaps and transverse gaps are connected; an artificial magnetic conductor periodic unit array layer is located on the upper surface of the second dielectric layer; a second metal ground covers the lower surface of the second dielectric layer; the first dielectric layer and the second dielectric layer are supported and connected by insulating pillars (plastic pillars are used in this embodiment), and a certain air layer is spaced between the first metal ground and the artificial magnetic conductor periodic unit structure.

[0042] The outer conductors of the two central SMA connectors 3 are connected to the artificial magnetic conductor reflector and the first metal ground. Their coaxial inner cores pass through the through holes of the artificial magnetic conductor reflector, the first metal ground, and the first dielectric layer in sequence and are connected to the two metal strips located on the upper surface of the first dielectric layer.

[0043] The first dielectric layer is made of F4B with a relative permittivity of 3.5, a thickness of 1 mm, and dimensions of 403.26 mm × 80 mm. The second dielectric layer is made of F4B with a relative permittivity of 3, a thickness of 1.5 mm, and dimensions of 403.26 mm × 120 mm. The height between the first and second dielectric layers is 5 mm, supported by plastic pillars.

[0044] The radio frequency signal is fed into the metal strip through the coaxial inner core of the SMA connector. After passing through the matching transition structure with gradually varying groove depth and width on both sides, it is fed into the artificial surface plasmon structure for energy transmission. When the electromagnetic wave reaches the ends of the artificial surface plasmon structures on both sides, the open circuit will generate a reflected wave, which will superimpose with the initial incident wave to form a standing wave.

[0045] The first metallic substrate is etched with slots to allow for fast-wave leakage radiation during slow-wave periodic modulation. Each modulation cycle contains a composite set of transverse and longitudinal slots connected together. For example... Figure 5 As shown in (a) and (b), the length of the transverse slit is It is also the width of the first metal ground, and the seam width is The left edge of the longitudinal seam is located at the center of the transverse seam and connects with it; the seam length is... The seam width is The longitudinal slit is located at the center of the transverse slit to make the two ports symmetrical. To achieve positive and negative 45° dual polarization, the two ports must be symmetrical with respect to the longitudinal slit, so that the electric field directions of the two ports in the longitudinal slit are opposite. This results in the combined electric field corresponding to the far-field polarization of 45° and -45°.

[0046] like Figure 6 The diagram shows the structure and parameters of an artificial surface plasmon cell. The cell period and width are respectively... and The width and depth of the slot are respectively and . Figure 6 The study also showed the dispersion curves of artificial surface plasmon cells with different groove depths. It can be seen that different groove depths correspond to different dispersion cutoff frequencies, which means that at the same frequency point, the phase constant of electromagnetic waves in the slow wave state can be controlled by changing the groove depth. Furthermore, the deeper the groove, the lower the cutoff frequency.

[0047] When the slot depth of the plasmonic structures on the artificial surfaces on both sides of the feed center is equal to the slot period of the first metallic ground, wide-side radiation within a certain frequency band can be achieved under the condition that the propagation constant of the fast wave after periodic modulation is reasonably designed. Furthermore, in order to achieve beam deflection, the slot depths of the plasmonic structures on the artificial surfaces on both sides of the feed center need to be different, respectively... and Meanwhile, the length and width of the gaps on both sides of the first metal base are the same, but the opening cycles are different, respectively. and ,like Figure 5 The slotting depth and the slit period of the artificial surface plasmon structure on the left side of the feed shown in (a) and (b) are respectively... and The slotting depth of the artificial surface plasmonic structure on the right side of the feed and the slotting period of the first metal ground are respectively... and This allows it to regulate the propagation constants on both sides, effectively forming an inclined equiphase surface, thereby generating a downward tilt angle.

[0048] The antenna downtilt design method includes: by designing the slot depth of the plasmonic structures on the artificial surfaces on both sides of the center feed and the slot period of the first metal ground, the propagation constants on both sides are controlled to form an equivalent tilted equiphase surface, thereby achieving 6° directional radiation of standing wave leakage waves with edge reflection effect in the 3.4-3.6GHz frequency band.

[0049] The method for adjusting the propagation constants on both sides is as follows: The normalized far-field radiation pattern is calculated based on the expression for the directional coefficient, and the theoretical downtilt angle is read from the pattern. If the theoretical angle deviates too much from the expected angle, the propagation constants on both sides are adjusted and substituted back into the expression for further calculation to obtain a new theoretical downtilt angle, until the error between the theoretical and expected angles meets the requirements. Guided by the theoretically required propagation constants on both sides at the obtained expected radiation angle, the slot depth of the plasmonic structures on the artificial surfaces on both sides of the feed center and the slotting period of the first metal ground are designed to ensure that the resulting propagation constants match the theory. Specifically:

[0050] Figure 7 This is a schematic diagram of the directional standing wave leaky wave antenna proposed in this invention. It can be seen that the propagation constants on the left and right sides of the feed are different, and are marked as follows: and ,in , This represents the attenuation constant of the transmission line on the left side of the feed. This represents the phase constant of the transmission line on the left side of the feed. This represents the attenuation constant of the transmission line on the right side of the feed. Let represent the phase constant of the transmission line on the right side of the feed; for this bidirectional leaky antenna, its initial aperture field distribution can be expressed as:

[0051] (1)

[0052] (2)

[0053] in, This indicates the initial aperture field distribution on the left side of the feed. This indicates the displacement relative to the feeder. Indicates the length from the feed to one end of the antenna. This represents the initial aperture field distribution on the right side of the feed.

[0054] Then, when the electromagnetic waves propagate to the edges on both sides = and When this happens, a reflected wave will be formed, and its aperture field distribution can be expressed as:

[0055] (3)

[0056] (4)

[0057] in, This indicates the aperture field distribution of the reflected wave on the left side of the feed. This represents the aperture field distribution of the reflected wave on the right side of the feed. and All are unknowns, each representing the past... and The amplitude of the propagating reflected wave. Therefore, the entire aperture field can be expressed as:

[0058] (5)

[0059] in, This represents the overall aperture field distribution.

[0060] Reflectance coefficient This represents the ratio between electromagnetic waves propagating in opposite directions at the edge reflection point. Since the end conditions of the plasmonic structures on both sides of the feed are open circuits in this embodiment, the reflection coefficient... Both are 1, at the left edge and the right edge of They can be represented as:

[0061] (6)

[0062] (7)

[0063] By solving equations (6) and (7) simultaneously, it is not difficult to find the unknown. and :

[0064] (8)

[0065] (9)

[0066] Based on the source field distribution obtained from the solution, its corresponding far-field radiation pattern can be obtained by Fourier transform:

[0067] (10)

[0068] in, Represents the far-field pattern function. This indicates the angle between the observation direction and the direction of the antenna normal. It is the propagation constant of electromagnetic waves in free space. Therefore, the directivity coefficient can be expressed as:

[0069] (11)

[0070] in, Indicates the directional coefficient. Indicates in Far-field pattern function in the direction, This represents the angle of the integral variable.

[0071] Guided by this standing wave leakage theory model with reflection effect, the propagation constants required on both sides of the feed to achieve the desired radiation angle can be easily known in advance. Based on this theoretical value, the slot depth of the plasmonic structure on the artificial surface on both sides of the feed center and the slot period of the first metal ground can be designed.

[0072] Figure 8 In Figure (a), the curves of the normalized phase constant and attenuation constant as a function of frequency are shown. These curves can be extracted and calculated along the near-field distribution of the plasmon structure on the artificial surface. Figure 8 Figure (b) shows the far-field radiation pattern obtained by substituting the extracted 3.5 GHz propagation constant into the formula for theoretical calculation. It can be seen that the main beam radiation angle is 6°, which is in good agreement with the simulation results. Therefore, the accuracy and precision of the theoretical model are verified.

[0073] Figure 9 Figures (a) and (b) show the electric field vector distribution near the 3.4 GHz center feed under different port excitations. Since the antenna is center-bottom fed, electromagnetic waves propagate in opposite directions to both sides after exiting the feed port. If the distances from the feed center to the first transverse slots on both sides are equal, the electric field vectors in the transverse and longitudinal slots will also be opposite due to the opposite propagation directions. Therefore, the electric field vectors in the transverse and longitudinal slots on both sides of the feed will be superimposed and have opposite directions, resulting in a radiation null point. Therefore, to ensure co-polarized radiation on both sides of the feed, the distances from the feed center to the first transverse slots on both sides need to be unequal, respectively... and This allows the introduced phase difference to cancel out the effects of the opposite propagation direction, achieving co-polarized radiation on both sides of the feed. For example... Figure 9 As shown in (a), when port 1 is excited, the electric field vector distribution diagram shows that the superposition of the electric fields in the gap results in a -45° polarization. Similarly, because the two metal strips are symmetrically distributed along the y-axis of the first dielectric layer, and the longitudinal gap is located between the two metal strips, when the two ports are excited, the electric field vectors in the transverse gap are in the same direction, while the electric field vectors in the longitudinal gap are in opposite directions. Therefore, as shown in (a), the electric field vectors in the transverse gap are in the same direction, while the electric field vectors in the longitudinal gap are in opposite directions. Figure 9 As shown in (b), it can be seen from the superposition of electric field vectors in the gap that the radiation emitted when port 2 is excited is 45° polarized.

[0074] To improve the radiation gain of the upper half-space and reduce the antenna profile, an artificial magnetic conductor reflector is placed beneath the first metallic ground. For example... Figure 10 The image shows a periodic square cell of an artificial magnetic conductor, with a square patch having a side length of [missing information]. and period is . Figure 10The reflection phase curve of the artificial magnetic conductor unit is also shown. This invention uses an in-phase reflection bandgap of an artificial magnetic conductor structure defined in the frequency range corresponding to 90°±45°. This definition takes into account antenna impedance matching and radiation efficiency, which is more in line with practical engineering applications.

[0075] Figure 11 (a) through (d) show the actual antennas that were fabricated. (a) shows the metal strip layer on the upper surface of the first dielectric layer, (b) shows the first metal ground with slots on the lower surface of the first dielectric layer, (c) shows the periodic unit array layer on the upper surface of the artificial magnetic conductor reflector, and (d) shows the overall effect after assembly by plastic pillars.

[0076] Figure 12 Figure (a) shows the simulated and measured reflection coefficients S11 and S22. It can be seen that the simulation and measured results are basically in agreement, both below -10 dB in the 3.4-3.6 GHz frequency band, indicating that good matching and efficient radiation can be achieved within the design frequency band. Figure 12 Figure (b) shows the isolation S21 and S12 between the simulation and the test. It can be seen that the simulation and test results are basically consistent, and both are below -20 dB in the 3.4-3.6 GHz frequency band, indicating that the isolation between ports is good within the design frequency band.

[0077] Figure 13 Tables (a) to (f) show a comparison of the simulated and tested far-field radiation patterns. (a) shows the simulated and tested far-field radiation patterns at 3.4 GHz with port 1 excitation and polarization of -45°; (b) shows the simulated and tested far-field radiation patterns at 3.5 GHz with port 1 excitation and polarization of -45°; (c) shows the simulated and tested far-field radiation patterns at 3.6 GHz with port 1 excitation and polarization of -45°; (d) shows the simulated and tested far-field radiation patterns at 3.4 GHz with port 2 excitation and polarization of 45°; (e) shows the simulated and tested far-field radiation patterns at 3.5 GHz with port 2 excitation and polarization of 45°; and (f) shows the simulated and tested far-field radiation patterns at 3.6 GHz with port 2 excitation and polarization of 45°. It can be seen that the simulated and measured results are basically consistent, especially in the range of 3.4-3.6 GHz. The radiation angle is 6° within the GHz band, with a deviation range of less than 1°, and the cross-polarization is greater than 16.8 dB.

[0078] This invention proposes a dual-polarized directional standing wave leaky wave antenna and a downtilt design method. It achieves fast-wave leaky wave radiation by etching slots in a metallic ground to control the slow-wave period. By rationally designing the distance from the feed center to the first transverse slot on both sides, it achieves co-polarized radiation on both sides of the feed. Furthermore, because the two metal strips are symmetrically distributed along the central axis, the electric field distribution in the longitudinal slot is opposite when excited at different ports. This, combined with the co-polarized electric field in the transverse slot, cleverly achieves... Dual polarization. Guided by theoretical models, the slot depth of the plasmonic structures on the artificial surfaces on both sides of the center feed and the slot period of the first metallic ground are designed respectively. The propagation constants on both sides are adjusted to effectively form an inclined equiphase surface, thereby achieving beam deflection within a certain operating bandwidth. An artificial magnetic conductor reflector is used to reduce the antenna profile. This invention extends the radiation performance of standing wave leaky wave antennas and overcomes the problems of large feed line usage and loss in traditional array antennas. It can be used as a basic unit of large-aperture high-gain base station array antennas and has important practical application value in point-to-point long-distance communication.

[0079] It should be emphasized that the above are merely examples of the present invention in the selected operating range of 3.4GHz-3.6GHz and a downtilt angle of 6°, and are not intended to limit the present invention in any way. Any simple modifications, equivalent changes and alterations made to the above examples at different frequencies or angles based on the technical essence of the present invention shall fall within the scope of the technical solution of the present invention.

[0080] The present invention also provides an electronic device, comprising:

[0081] Memory, used to store computer programs;

[0082] A processor for executing the computer program to implement the method.

[0083] The present invention also provides a non-volatile storage medium for storing a computer program, wherein the computer program implements the method when executed by a processor.

[0084] The present invention also provides a computer program product, including a computer program / instructions that, when executed by a processor, implement the method described.

Claims

1. A dual-polarized directional standing wave leaky antenna, characterized in that, include: The system comprises a metal strip layer, a first dielectric layer, a first metal ground, and an artificial magnetic conductor reflector. The metal strip layer is located on the upper surface of the first dielectric layer and includes two metal strips symmetrically distributed along the central axis of the first dielectric layer in the y-direction. Each metal strip includes a matching transition structure and an artificial surface plasmon structure with open ends. The groove depths of the artificial surface plasmon structures on both sides of the feed center are different. The first metal ground is etched with periodic composite slots. The distances from the feed center to the composite slots on both sides are different, and the slot periods on both sides of the feed center are different. An air layer separates the first metal ground and the artificial magnetic conductor reflector. The radio frequency signal sequentially passes through the vias of the artificial magnetic conductor reflector and the vias of the first metal ground and the first dielectric layer to connect with the feed centers of the two metal strips. After passing through the matching transition structures on both sides, the signal is fed into the artificial surface plasmon structures on both sides.

2. The dual-polarized directional standing wave leaky wave antenna according to claim 1, characterized in that, The composite gap of the first metal ground includes a transverse gap and a longitudinal gap, with the centers of the longitudinal gap and the transverse gap connected.

3. A dual-polarized directional standing wave leaky antenna according to claim 2, characterized in that, The distance from the power supply center to the first transverse gap on each side is different.

4. The dual-polarized directional standing wave leaky wave antenna according to claim 1, characterized in that, The artificial magnetic conductor reflector comprises, from top to bottom, an array layer of periodic artificial magnetic conductor units, a second dielectric layer, and a second metal ground.

5. A dual-polarized directional standing wave leaky antenna according to claim 4, characterized in that, The periodic unit of the artificial magnetic conductor is a square patch, and the size of the square patch and the period of the unit meet the reflection phase requirements in the operating frequency band.

6. The downtilt angle design method for the dual-polarized directional standing wave leaky wave antenna according to any one of claims 1-5, characterized in that, include: By designing the slot depth of the plasmonic structures on the artificial surfaces on both sides of the feed center and the slit period of the first metal ground, the propagation constants on both sides are controlled, effectively forming an inclined equiphase surface, which directionally radiates a standing wave leakage wave with edge reflection effect within a preset frequency band.

7. The method according to claim 6, characterized in that, The method for adjusting the propagation constants on both sides is as follows: Calculate the normalized far-field radiation pattern based on the expression for the directional coefficient, and read the theoretical downtilt angle from the pattern; if the theoretical angle deviates too much from the expected angle, adjust the propagation constants on both sides and substitute them into the expression again, and further calculate and read the new theoretical downtilt angle until the error between the theoretical angle and the expected angle meets the requirements; under the guidance of the propagation constants on both sides required by theory at the obtained expected radiation angle, design the slot depth of the plasmonic structure on the artificial surface on both sides of the feed center and the slotting period of the first metal ground, so that the resulting propagation constant matches the theory; The expression for the directionality coefficient is: ； in, Indicates the directional coefficient. Indicates in Far-field pattern function in the direction, Represents the angle of the integral variable. Represents the far-field pattern function. Indicates the angle between the observation direction and the direction of the antenna normal; ； in, Indicates the overall aperture field distribution. This indicates the displacement relative to the feeder. Indicates the length from the feed to one end of the antenna. and Let these represent the propagation constants on both sides. and They represent going to and The amplitude of the propagating reflected wave, It is the propagation constant of electromagnetic waves in free space.

8. An electronic device, characterized in that, include: Memory, used to store computer programs; A processor for executing the computer program to implement the method as described in any one of claims 6 to 7.

9. A non-volatile storage medium, characterized in that, Used to store a computer program, wherein the computer program, when executed by a processor, implements the method as described in any one of claims 6 to 7.

10. A computer program product comprising a computer program / instructions, characterized in that, When the computer program / instructions are executed by the processor, they implement the method described in any one of claims 6 to 7.

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