Receiving method

Abstract

The codeword length of the block code and the bit length required for mapping according to the modulation method are adjusted. [Solution] The transmitting device includes a coding unit that generates a plurality of coded blocks, each of which is generated from an information sequence including a portion of a data stream; a bit length adjusting unit that generates a plurality of adjusted bit sequences by adding a known bit sequence to each of the coded blocks; a mapping unit that modulates the plurality of adjusted bit sequences using a first modulation method selected from a plurality of modulation methods to generate a plurality of modulation symbols; and a transmitting unit that transmits a frame signal including the plurality of modulation symbols.

Description

[Technical Field]

[0001] (Reference to Related Applications) The disclosures of the claims, specifications, drawings and abstracts contained in Japanese Patent Application No. 2013-003905 filed on January 11, 2013, Japanese Patent Application No. 2013-033353 filed on February 22, 2013, and Japanese Patent Application No. 2013-195166 filed on September 20, 2013 are incorporated herein by reference in their entirety. The present invention relates to a data processing method, a precoding method, and a communication device. [Background technology]

[0002] Conventionally, a communication method using multiple antennas is known as a communication method called MIMO (Multiple-Input Multiple-Output). In multi-antenna communications, such as MIMO, one or more streams of transmission data are modulated and each modulated signal is transmitted simultaneously from different antennas using the same frequency (common frequency), thereby improving the reception quality of the data and / or increasing the data communication speed (per unit time).

[0003] 72 is a diagram illustrating an overview of the spatial multiplexing MIMO system. The MIMO system in the diagram shows an example of the configuration of a transmission / reception device when the number of transmission antennas is two (TX1, TX2), the number of reception antennas is two (RX1, RX2), and the number of transmission modulated signals (transmission streams) is two. The transmitting device includes a signal generating unit and a radio processing unit. The signal generator performs channel coding on the data, performs MIMO precoding, and generates two transmit signals z1(t) and z2(t) that can be transmitted simultaneously using the same frequency (common frequency). The radio processor multiplexes the individual transmit signals in the frequency domain as necessary, i.e., converts them into multi-carrier signals (e.g., using OFDM), and inserts pilot signals that allow the receiver to estimate channel distortion, frequency offset, phase distortion, and the like. (Note that the pilot signals may also be used to estimate other distortions, and the receiver may also use the pilot signals for signal detection. Note that the use of pilot signals in the receiver is not limited to this.) The transmitter transmits z1(t) and z2(t) using two antennas (TX1 and TX2). The receiving device includes receiving antennas (RX1 and RX2), a radio processing unit, a channel fluctuation estimation unit, and a signal processing unit. The receiving antenna (RX1) receives signals transmitted from two transmitting antennas (TX1 and TX2) of the transmitting device. The channel fluctuation estimation unit estimates channel fluctuation values ​​using pilot signals and supplies the channel fluctuation estimates to the signal processing unit. The signal processing unit restores the data contained in z1(t) and z2(t) based on the signals received by the two receiving antennas and the estimated channel values, and obtains this as one received data. However, the received data may be hard decision values ​​of "0" or "1", or soft decision values ​​such as log-likelihood or log-likelihood ratio. Furthermore, various encoding methods such as turbo codes and low-density parity-check (LDPC) codes are used (Non-Patent Documents 1 and 2). [Prior art documents] [Non-patent literature]

[0004] [Non-Patent Document 1] RG Gallager, “Low-density parity-check codes,” IRE Trans. Inform. Theory, IT-8, pp-21-28, 1962. [Non-patent document 2] “Performance analysis and design optimization of LDPC-coded MIMO OFDM systems” IEEE Trans. Signal Processing., vol.52, no.2, pp.348-361, Feb. 2004. [Non-patent document 3] C. Douillard, and C. Berrou, “Turbo codes with rate-m / (m+1) constituent convolutional codes,” IEEE Trans. Commun., vol.53, no.10, pp.1630-1638, Oct. 2005. [Non-patent document 4] C. Berrou, “The ten-year-old turbo codes are entering into service,” IEEE Communication Magazine, vol.41, no.8, pp.110-116, Aug. 2003. [Non-Patent Document 5] DVB Document A122, Framing structure, channel coding and modulation for a second generation digital terrestrial television broadcasting system (DVB-T2), June 2008. [Non-patent document 6] DJC Mackay, “Good error-correcting codes based on very sparse matrices,” IEEE Trans. Inform. Theory, vol.45, no.2, pp399-431, March 1999. [Non-Patent Document 7] SMAlamouti, “A simple transmit diversity technique for wireless communications,” IEEE J. Select. Areas Commun., vol.16, no.8, pp.1451-1458, Oct 1998. [Non-patent document 8] V. Tarokh, H. Jafrkhani, and ARCalderbank, “Space-time block coding for wireless communications: Performance results,” IEEE J. Select. Areas Commun., vol.17, no.3, no.3, pp.451―460, March 1999. Summary of the Invention [Problem to be solved by the invention]

[0005] The present invention solves the implementation problems that arise when applying a coding method such as an LDPC code when using a MIMO system. [Means for solving the problem]

[0006] The data processing method according to the present invention includes: an encoding step of outputting a first bit string (503) that is an N-bit code word from a K-bit information bit string; a mapping step of generating a first complex signal s1 and a second complex signal s2 using a bit string of (X+Y) bits obtained from an input second bit string, where X is a first number of bits for generating a first complex signal s1 and Y is a second number of bits for generating a second complex signal s2; and a bit length adjustment step of adjusting the first bit string so that the length of the second bit string is a multiple of (X+Y) bits after the encoding step but before the mapping step, and outputting the adjusted first bit string. [Effects of the Invention]

[0007] The data processing method according to the present invention can contribute to solving implementation issues when applying a coding method such as an LDPC code when using a MIMO system. [Brief explanation of the drawings]

[0008] [Figure 1] Example of a QPSK signal constellation in the IQ plane [Figure 2] Example of a 16QAM signal constellation in the IQ plane [Figure 3] Example of a 64QAM signal constellation in the IQ plane [Figure 4] An example of a 256QAM signal constellation in the IQ plane [Figure 5] Example of transmitter configuration [Figure 6] Example of transmitter configuration [Figure 7] Example of transmitter configuration [Figure 8] Example of signal processing unit configuration [Figure 9] Frame configuration example [Figure 10] Example of a 16QAM signal constellation in the IQ plane [Figure 11] Example of a 64QAM signal constellation in the IQ plane [Figure 12] Example of a signal constellation in the IQ plane [Figure 13] Example of a signal constellation in the IQ plane [Figure 14] Example of a signal constellation in the IQ plane [Figure 15] Example of a signal constellation in the IQ plane [Figure 16] Example of a signal constellation in the IQ plane [Figure 17] Example of a signal constellation in the IQ plane [Figure 18] Example of a signal constellation in the IQ plane [Figure 19] Example of a signal constellation in the IQ plane [Figure 20] Example of a signal constellation in the IQ plane [Figure 21]An example of a signal constellation in the first quadrant of the IQ plane [Figure 22] Example of a signal constellation in the second quadrant of the IQ plane [Figure 23] Example of a signal constellation in the third quadrant of the IQ plane [Figure 24] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 25] An example of a signal constellation in the first quadrant of the IQ plane [Figure 26] Example of a signal constellation in the second quadrant of the IQ plane [Figure 27] Example of a signal constellation in the third quadrant of the IQ plane [Figure 28] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 29] An example of a signal constellation in the first quadrant of the IQ plane [Figure 30] Example of a signal constellation in the second quadrant of the IQ plane [Figure 31] Example of a signal constellation in the third quadrant of the IQ plane [Figure 32] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 33] An example of a signal constellation in the first quadrant of the IQ plane [Figure 34] Example of a signal constellation in the second quadrant of the IQ plane [Figure 35] Example of a signal constellation in the third quadrant of the IQ plane [Figure 36] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 37] An example of a signal constellation in the first quadrant of the IQ plane [Figure 38] Example of a signal constellation in the second quadrant of the IQ plane [Figure 39] Example of a signal constellation in the third quadrant of the IQ plane [Figure 40] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 41] An example of a signal constellation in the first quadrant of the IQ plane [Figure 42]Example of a signal constellation in the second quadrant of the IQ plane [Figure 43] Example of a signal constellation in the third quadrant of the IQ plane [Figure 44] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 45] An example of a signal constellation in the first quadrant of the IQ plane [Figure 46] Example of a signal constellation in the second quadrant of the IQ plane [Figure 47] Example of a signal constellation in the third quadrant of the IQ plane [Figure 48] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 49] An example of a signal constellation in the first quadrant of the IQ plane [Figure 50] Example of a signal constellation in the second quadrant of the IQ plane [Figure 51] Example of a signal constellation in the third quadrant of the IQ plane [Figure 52] Example of a signal constellation in the fourth quadrant of the IQ plane [Figure 53] Diagram showing the relationship between transmitting and receiving antennas [Figure 54] Example of receiving device configuration [Figure 55] Example of a signal constellation in the IQ plane [Figure 56] Example of a signal constellation in the IQ plane [Figure 57] 1 is a block diagram showing a part of a transmitter according to a first embodiment that generates a modulated signal; [Figure 58] Flow diagram of a method for generating a modulated signal [Figure 59] Flow diagram of bit length adjustment processing according to the first embodiment [Figure 60] Configuration of the modulation unit of the second embodiment [Figure 61] Example of a parity check matrix [Figure 62] Example of constructing a submatrix [Figure 63] Flow diagram of LDPC encoding processing executed by encoding unit 502LA [Figure 64]1 is a diagram showing an example of a configuration for realizing the above-mentioned accumulation process. [Figure 65] Flow diagram of bit length adjustment processing according to the second embodiment [Figure 66] Example of how to generate a bit string for adjustment [Figure 67] Example of how to generate a bit string for adjustment [Figure 68] Example of how to generate a bit string for adjustment [Figure 69] Modification of the adjusted bit string generated by the bit length adjustment unit [Figure 70] Modification of the adjusted bit string generated by the bit length adjustment unit [Figure 71] FIG. 1 is a diagram illustrating one of the features of the invention according to embodiment 2. [Figure 72] MIMO system overview [Figure 73] Configuration diagram of a modulation unit according to the third embodiment [Figure 74] A diagram illustrating the operation of bit interleaver 502BI using output bit strings. [Figure 75] Example of implementation of bit interleaver 502 [Figure 76] Example of bit length adjustment processing [Figure 77] A diagram showing an example of a bit string to be added [Figure 78] Example of inserting a bit string adjustment part [Figure 79] Modification of the Modulation Section [Figure 80] Configuration diagram of a modulation unit according to the fourth embodiment [Figure 81] Flow diagram showing the process [Figure 82] A diagram showing the relationship between the length of the BBFRAME (K bits) and the length of the reserved TmpPadNum [Figure 83] Modulation section configuration different from that of Figure 80 [Figure 84] A diagram explaining the bit lengths of bit strings 501 to 8003 [Figure 85] Example of a bitstream decoding unit in a receiving device [Figure 86] A diagram explaining the input and output of the bit string adjustment unit [Figure 87] Example of a bitstream decoding unit in a receiving device [Figure 88] Example of a bitstream decoding unit in a receiving device [Figure 89] FIG. 20 is a diagram conceptually explaining the processing of the sixth embodiment. [Figure 90] A diagram showing the relationship between a transmitting device and a receiving device. [Figure 91] Example of the configuration of the modulation section on the transmitting side [Figure 92] Diagram showing the bit length of each bit string [Figure 93] Configuration diagram of the modulation section on the transmitting side different from that shown in Figure 91 [Figure 94] Diagram showing the bit length of each bit string [Figure 95] Diagram showing the bit length of each bit string [Figure 96] Example of a bitstream decoding unit in a receiving device [Figure 97] Diagram of the part that processes precoding [Figure 98] Diagram of the part that processes precoding [Figure 99] An example of the configuration of the signal processing unit [Figure 100] An example of a time-frequency frame structure for transmitting two streams [Figure 101] (A) A diagram showing the state of the first bit string 503 to be output, and (B) A diagram showing the state of the second bit string 5703 to be output. [Figure 102] (A) A diagram showing the state of the first bit string 503 to be output, and (B) A diagram showing the state of the second bit string 5703 to be output. [Figure 103] (A) A diagram showing the state of the first bit string 503Λ that is output, and (B) A diagram showing the state of the bit string 7303 that has been output after bit length adjustment. [Figure 104] (A) A diagram showing the state of the first bit string 503′ (or 503Λ) to be output, (B) A diagram showing the state of the bit string 8003 after the bit length has been adjusted to be output. [Figure 105](A) A diagram showing the state of an N-bit codeword 503 that is output. (B) A diagram showing the state of an N-PunNum-bit data string 9102 that is output. [Figure 106] Overview of frame configuration [Figure 107] An example of two or more types of signals occurring at the same time [Figure 108] An example of the configuration of a transmitting device [Figure 109] Frame configuration example [Figure 110] Example of receiving device configuration [Figure 111] Example of a 16QAM signal constellation in the IQ plane [Figure 112] Example of a 64QAM signal constellation in the IQ plane [Figure 113] An example of a 256QAM signal constellation in the IQ plane [Figure 114] Example of a 16QAM signal constellation in the IQ plane [Figure 115] Example of a 64QAM signal constellation in the IQ plane [Figure 116] An example of a 256QAM signal constellation in the IQ plane [Figure 117] An example of the configuration of a transmitting device [Figure 118] An example of the configuration of a receiving device [Figure 119] Example of a 16QAM signal constellation in the IQ plane [Figure 120] Example of a 64QAM signal constellation in the IQ plane [Figure 121] An example of a 256QAM signal constellation in the IQ plane [Figure 122] An example of the configuration of a transmitting device [Figure 123] An example of a frame configuration [Figure 124] An example of the configuration of a receiving device [Figure 125] An example of the configuration of a transmitting device [Figure 126] An example of a frame configuration [Figure 127] An example of the configuration of a receiving device [Figure 128]Diagram explaining a transmission method using space-time block codes [Figure 129] An example of the configuration of a transmitting device [Figure 130] An example of the configuration of a transmitting device [Figure 131] An example of the configuration of a transmitting device [Figure 132] An example of the configuration of a transmitting device [Figure 133] Diagram explaining a transmission method using space-time block codes DETAILED DESCRIPTION OF THE INVENTION

[0009] Before describing each embodiment of the present invention, we will explain a transmission method and a reception method to which the inventions described in the following embodiments can be applied, as well as examples of the configurations of a transmission device and a reception device that use them. (Configuration example R1) FIG. 5 shows an example of the configuration of a part that generates a modulated signal when the transmission method can be switched in a transmitting device of a base station (broadcast station, access point, etc.).

[0010] In this configuration example, one of the switchable transmission methods is a transmission method for transmitting two streams (MIMO (Multiple Input Multiple Output) method). A transmission method in which a transmitting device of a base station (broadcast station, access point, etc.) transmits two streams will be described with reference to FIG. Encoding section 502 in FIG. 5 receives information 501 and control signal 512 as input, performs encoding based on the information on the coding rate and code length (block length) included in control signal 512, and outputs encoded data 503.

[0011] Mapping section 504 receives encoded data 503 and control signal 512 as input. Control signal 512 specifies that two streams are to be transmitted as the transmission method. In addition, control signal 512 specifies modulation method α and modulation method β as the modulation methods for each of the two streams. Note that modulation method α is a modulation method for modulating x-bit data, and modulation method β is a modulation method for modulating y-bit data. (For example, 16QAM (16 Quadrature Amplitude Modulation) is a modulation method for modulating 4-bit data, and 64QAM (64 Quadrature Amplitude Modulation) is a modulation method for modulating 6-bit data.) Then, mapping unit 504 modulates x bits of data out of the x+y bits of data using modulation method α to generate and output baseband signal s1(t) (505A), and also modulates the remaining y bits of data using modulation method β to output baseband signal s2(t) (505B). (Note that while FIG. 5 shows one mapping unit, an alternative configuration may include separate mapping units for generating s1(t) and s2(t). In this case, coded data 503 is distributed to the mapping unit for generating s1(t) and the mapping unit for generating s2(t).) Note that s1(t) and s2(t) are expressed as complex numbers (however, they may be either complex or real numbers), and t is time. Note that when a transmission method using multicarriers such as OFDM (Orthogonal Frequency Division Multiplexing) is used, s1 and s2 can be considered as functions of frequency f, such as s1(f) and s2(f), or as functions of time t and frequency f, such as s1(t,f) and s2(t,f). In the following, the baseband signal, precoding matrix, phase change, etc. are described as functions of time t, but they may also be considered as functions of frequency f, or functions of time t and frequency f. Therefore, although the baseband signal, precoding matrix, phase change, and the like are sometimes described as functions of symbol number i, in this case they can be considered as functions of time t, functions of frequency f, or functions of time t and frequency f. That is, the symbols and baseband signals may be generated and arranged in the time axis direction, or may be generated and arranged in the frequency axis direction. Furthermore, the symbols and baseband signals may be generated and arranged in both the time axis direction and the frequency axis direction.

[0012] Power change unit 506A (power adjustment unit 506A) receives baseband signal s1(t) (505A) and control signal 512, sets real number P1 based on control signal 512, and outputs P1×s1(t) as power-changed signal 507A. (Note that although P1 is a real number, it may also be a complex number.) Similarly, power change unit 506B (power adjustment unit 506B) receives baseband signal s2(t) (505B) and control signal 512, sets real number P2, and outputs P2×s2(t) as power-changed signal 507B. (Note that although P2 is a real number, it may also be a complex number.) Weighting combination unit 508 receives power-modified signal 507A, power-modified signal 507B, and control signal 512 as input, and sets precoding matrix F (or F(i)) based on control signal 512. Assuming that the slot number (symbol number) is i, weighting combination unit 508 performs the following calculation.

[0013]

number

[0014] Here, a(i), b(i), c(i), and d(i) can be expressed as complex numbers (or real numbers), and three or more of a(i), b(i), c(i), and d(i) must not be 0 (zero). Note that the precoding matrix may or may not be a function of i. When the precoding matrix is ​​a function of i, the precoding matrix switches depending on the slot number (symbol number).

[0015] Then, weighting and combining section 508 outputs u1(i) in equation (R1) as weighted and combined signal 509A, and outputs u2(i) in equation (R1) as weighted and combined signal 509B. Power modification section 510A receives weighted and combined signal 509A (u1(i)) and control signal 512 as input, sets real number Q1 based on control signal 512, and outputs Q1×u1(t) as power-modified signal 511A (z1(i)). (Note that although Q1 is a real number, it may also be a complex number.) Similarly, power modification section 510B receives weighted and combined signal 509B (u2(i)) and control signal 512 as input, sets real number Q2 based on control signal 512, and outputs Q2×u2(t) as power-modified signal 511A (z2(i)). (Note that although Q2 is a real number, it may also be a complex number.) Therefore, the following equation holds:

[0016]

number

[0017] Next, a transmission method for transmitting two streams different from those in Fig. 5 will be described with reference to Fig. 6. In Fig. 6, components that operate in the same manner as in Fig. 5 are given the same reference numerals. Phase change unit 501 receives signal 509B after weighting and combining u2(i) in equation (R1) and control signal 512 as input, and changes the phase of signal 509B after weighting and combining u2(i) in equation (R1) based on control signal 512. Therefore, the signal after changing the phase of signal 509B after weighting and combining u2(i) in equation (R1) is e jθ(i) ×u2(i), and e jθ(i) The phase change unit 601 outputs ×u2(i) as the phase-changed signal 602 (j is the imaginary unit). Note that the value of the phase to be changed is a function of i, such as θ(i).

[0018] 6 each change the power of the input signal. Therefore, the outputs z1(i) and z2(i) of the power modifying units 510A and 510B in FIG. 6 are expressed by the following equations:

[0019]

number

[0020] As a method of realizing equation (R3), there is a configuration shown in Figure 7 that differs from that shown in Figure 6. The difference between Figure 6 and Figure 7 is that the order of the power change section and the phase change section is swapped. (The functions of changing the power and phase remain the same.) In this case, z1(i) and z2(i) are expressed as follows:

[0021]

number

[0022] Note that z1(i) in formula (R3) is equal to z1(i) in formula (R4), and z2(i) in formula (R3) is equal to z2(i) in formula (R4). If the phase value θ(i) to be changed in equations (R3) and (R4) is set so that θ(i+1)−θ(i) is a fixed value, the receiving device is likely to obtain good data reception quality in a radio wave propagation environment dominated by direct waves. However, the method for setting the phase value θ(i) to be changed is not limited to this example.

[0023] FIG. 8 shows an example of the configuration of a signal processing unit that processes the signals z1(i) and z2(i) obtained from FIGS. Insertion unit 804A receives signal z1(i) (801A), pilot symbol 802A, control information symbol 803A, and control signal 512 as input, inserts pilot symbol 802A and control information symbol 803A into signal (symbol) z1(i) (801A) in accordance with the frame configuration included in control signal 512, and outputs modulated signal 805A in accordance with the frame configuration.

[0024] The pilot symbols 802A and the control information symbols 803A are symbols modulated by BPSK (Binary Phase Shift Keying) or QPSK (Quadrature Phase Shift Keying) or the like (other modulation methods may also be used). Radio unit 806A receives modulated signal 805A and control signal 512 as input, and performs processing such as frequency conversion and amplification on modulated signal 805A based on control signal 512 (when OFDM is used, processing such as inverse Fourier transform is performed), and outputs transmission signal 807A, which is output as radio waves from antenna 808A.

[0025] Insertion unit 804B receives signal z2(i) (801B), pilot symbol 802B, control information symbol 803B, and control signal 512 as input, inserts pilot symbol 802B and control information symbol 803B into signal (symbol) z2(i) (801B) in accordance with the frame configuration included in control signal 512, and outputs modulated signal 805B in accordance with the frame configuration.

[0026] The pilot symbols 802B and the control information symbols 803B are symbols modulated by BPSK (Binary Phase Shift Keying) or QPSK (Quadrature Phase Shift Keying) or the like (other modulation methods may also be used). Radio unit 806B receives modulated signal 805B and control signal 512 as input, and performs processing such as frequency conversion and amplification on modulated signal 805B based on control signal 512 (when OFDM is used, processing such as inverse Fourier transform is performed), and outputs transmission signal 807B, which is output as radio waves from antenna 808B.

[0027] Here, signals z1(i) (801A) and z2(i) (801B) with the same i number are transmitted from different antennas at the same time using the same (common) frequency. (In other words, this is a transmission method using the MIMO system.) Furthermore, pilot symbol 802A and pilot symbol 802B are symbols used in the receiving device for signal detection, frequency offset estimation, gain control, channel estimation, etc., and although they are called pilot symbols here, they may also be called reference symbols or other names.

[0028] Control information symbol 803A and control information symbol 803B are symbols for transmitting to the receiving device information on the modulation method used by the transmitting device, information on the transmission method, information on the precoding method, information on the error correction code method, information on the coding rate of the error correction code, information on the block length (code length) of the error correction code, etc. Note that the control information symbol may be transmitted using only one of control information symbol 803A and control information symbol 803B.

[0029] Figure 9 shows an example of a time-frequency frame structure when transmitting two streams. In Figure 9, the horizontal axis represents frequency and the vertical axis represents time. As an example, the symbol structure for carrier 1 to carrier 38 and time $1 to time $11 is shown. FIG. 9 shows the frame structure of the transmission signal transmitted from antenna 806A in FIG. 8 and the frame of the transmission signal transmitted from antenna 808B at the same time.

[0030] In Fig. 9, in the case of a frame of a transmission signal transmitted from antenna 806A in Fig. 8, the data symbol corresponds to signal (symbol) z1(i), and the pilot symbol corresponds to pilot symbol 802A. In Fig. 9, in the case of a frame of a transmission signal transmitted from antenna 806B in Fig. 8, the data symbol corresponds to signal (symbol) z2(i), and the pilot symbol corresponds to pilot symbol 802B.

[0031] (Therefore, as explained above, in signal z1(i) (801A) and signal z2(i) (801B), signals z1(i) (801A) and z2(i) (801B) with the same i number are transmitted from different antennas at the same time using the same (common) frequency. Also, the configuration of the pilot symbols is not limited to that shown in FIG. 9, and for example, the time interval and frequency interval of the pilot symbols are not limited to that shown in FIG. 9. In addition, in FIG. 9, signals are transmitted from antenna 806A in FIG. 8 and antenna 806B in FIG. 8 at the same time using the same frequency (same (sub)carrier). Although the frame configuration is such that pilot symbols are transmitted, the present invention is not limited to this. For example, a pilot symbol may be placed on antenna 806A in FIG. 8 at time A, frequency a ((sub)carrier a), and no symbol may be placed on antenna 806B in FIG. 8 at time A, frequency a ((sub)carrier a), and no symbol may be placed on antenna 806A in FIG. 8 at time B, frequency b ((sub)carrier b), and pilot symbols may be placed on antenna 806B in FIG. 8 at time B, frequency b ((sub)carrier b).

[0032] Although only data symbols and pilot symbols are shown in FIG. 9, other symbols, such as control information symbols, may also be included in the frame. Although the examples shown in FIGS. 5 to 7 have been described with some (or all) of the power adjustment units present, it is also possible that some of the power adjustment units are absent. For example, in FIG. 5, if power change section 506A (power adjustment section 506A) and power change section 506B (power adjustment section 506B) do not exist, z1(i) and z2(i) are expressed as follows:

[0033]

number

[0034] Furthermore, in FIG. 5, if power change section 510A (power adjustment section 510A) and power change section 510B (power adjustment section 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0035]

number

[0036] Furthermore, in FIG. 5, if power changing unit 506A (power adjustment unit 506A), power changing unit 506B (power adjustment unit 506B), power changing unit 510A (power adjustment unit 510A), and power changing unit 510B (power adjustment unit 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0037]

number

[0038] Furthermore, in FIG. 6 or FIG. 7, if power change section 506A (power adjustment section 506A) and power change section 506B (power adjustment section 506B) are not present, z1(i) and z2(i) are expressed as follows:

[0039]

number

[0040] Furthermore, in FIG. 6 or FIG. 7, if power change section 510A (power adjustment section 510A) and power change section 510B (power adjustment section 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0041]

number

[0042] 6 or 7, if the power changing unit 506A (power adjustment unit 506A), the power changing unit 506B (power adjustment unit 506B), the power changing unit 510A (power adjustment unit 510A), and the power changing unit 510B (power adjustment unit 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0043]

number

[0044] Next, mapping methods for QPSK, 16QAM, 64QAM, and 256QAM will be described as examples of mapping methods for modulation schemes for generating baseband signal s1(t) (505A) and baseband signal s2(t) (505B). The mapping method for QPSK will now be explained. Figure 1 shows an example of a QPSK signal point arrangement on the in-phase (I)-quadrature (Q) plane. In Figure 1, the four circles represent QPSK signal points, with I on the horizontal axis and Q on the vertical axis.

[0045] The coordinates of the four signal points of QPSK (the "○" in Figure 1 are signal points) on the in-phase I-quadrature Q plane are (w q ,w q ), (-w q ,w q ), (w q ,-w q ), (-w q ,-w q) becomes (w q is a real number greater than 0. Here, the bits to be transmitted (input bits) are assumed to be b0 and b1. For example, if the bits to be transmitted are (b0, b1)=(0, 0), they are mapped to signal point 501 in FIG. 1. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q)=(w q ,w q )

[0046] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in QPSK modulation) are determined based on the bits (b0, b1) to be transmitted. An example of the relationship between the set of b0 and b1 (0 0 to 1 1) and the coordinates of the signal points is shown in Figure 1. The four signal points of QPSK ("○" in Figure 1) (w q ,w q ), (-w q ,w q ), (w q ,-w q ), (-w q ,-w q ), the values ​​of the set 0 0 to 1 1 of b0 b1 are shown directly below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("circles") directly above the set 0 0 to 1 1 of b0 b1 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0 b1 (0 0 to 1 1) and the coordinates of the signal points in the case of QPSK is not limited to that shown in Figure 1. The complex representations of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of QPSK modulation) become the baseband signal (s1(t) or s2(t)).

[0047] The mapping method for 16QAM will now be explained. Figure 2 shows an example of a 16QAM signal point arrangement on the in-phase (I)-quadrature (Q) plane. In Figure 2, the 16 circles represent 16QAM signal points, with I on the horizontal axis and Q on the vertical axis.

[0048] The coordinates of the 16 signal points of 16QAM (the "circles" in Figure 2 are signal points) on the in-phase I-quadrature Q plane are (3w 16 ,3w 16 ), (3w 16 ,w 16 ), (3w 16 ,-w 16 ), (3w 16 ,-3w 16 ), (w 16 ,3w 16 ), (w 16 ,w 16 ), (w 16 ,-w 16 ), (w 16 ,-3w 16 ), (―w 16 ,3w 16 ), (―w 16 ,w 16 ), (―w 16 ,-w 16 ), (―w 16 ,-3w 16 ), (―3w 16 ,3w 16 ), (―3w 16 ,w 16 ), (―3w 16 ,-w 16 ), (―3w 16 ,-3w 16 ), and (w 16 is a real number greater than 0.

[0049] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, and b3. For example, if the bits to be transmitted are (b0, b1, b2, b3) = (0, 0, 0, 0), they are mapped to signal point 201 in FIG. 2. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (3w 16 ,3w 16 ) That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 16QAM) are determined based on the bits (b0, b1, b2, b3) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3 (0000 to 1111) and the coordinates of the signal points is shown in Figure 2. The 16 signal points ("○" in Figure 2) of 16QAM (3w16 ,3w 16 ), (3w 16 ,w 16 ), (3w 16 ,-w 16 ), (3w 16 ,-3w 16 ), (w 16 ,3w 16 ), (w 16 ,w 16 ), (w 16 ,-w 16 ), (w 16 ,-3w 16 ), (―w 16 ,3w 16 ), (―w 16 ,w 16 ), (―w 16 ,-w 16 ), (―w 16 ,-3w 16 ), (―3w 16 ,3w 16 ), (―3w 16 ,w 16 ), (―3w 16 ,-w 16 ), (―3w 16 ,-3w 16 ), the values ​​of the set 0000 to 1111 of b0, b1, b2, and b3 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal point ("○") immediately above the set 0000 to 1111 of b0, b1, b2, and b3 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, and b3 (0000 to 1111) and the signal point coordinates in the case of 16QAM is not limited to that shown in FIG. 2. The complex representation of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 16QAM) becomes the baseband signal (s1(t) or s2(t)).

[0050] The mapping method for 64QAM will now be explained. Figure 3 shows an example of a 64QAM signal point arrangement on the in-phase (I)-quadrature (Q) plane. In Figure 3, the 64 circles represent 64QAM signal points, with I on the horizontal axis and Q on the vertical axis. The coordinates of the 64 signal points of 64QAM (the "circles" in Figure 3 are signal points) on the in-phase I-quadrature Q plane are as follows: (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64 ,-w 64 ), (7w 64 ,-3w 64 ), (7w 64 ,―5w 64 ), (7w 64 ,―7w 64 ) (5w 64 ,7w 64 ), (5w 64 ,5w 64 ), (5w 64 ,3w 64 ), (5w 64 ,w 64 ), (5w 64 ,-w 64 ), (5w 64 ,-3w 64 ), (5w 64 ,―5w 64 ), (5w 64 ,―7w 64 ) (3w 64 ,7w 64 ), (3w 64 ,5w 64 ), (3w 64 ,3w 64 ), (3w 64 ,w 64 ), (3w 64 ,-w 64 ), (3w 64 ,-3w 64 ), (3w 64 ,―5w 64 ), (3w 64 ,―7w 64 ) (w 64 ,7w 64 ), (w 64 ,5w 64 ), (w64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64 ,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w 64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w 64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w 64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w64 ), (-5w 64 ,―5w 64 ), (-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 ), (-7w 64 ,5w 64 ), (-7w 64 ,3w 64 ), (-7w 64 ,w 64 ), (-7w 64 ,-w 64 ), (-7w 64 ,-3w 64 ), (-7w 64 ,―5w 64 ), (-7w 64 ,―7w 64 ) (w 64 is a real number greater than 0.

[0051] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, and b5. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), they are mapped to signal point 301 in FIG. 3. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (7w 64 ,7w 64 )

[0052] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the bits (b0, b1, b2, b3, b4, b5) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3, b4, b5 (000000 to 111111) and the coordinates of the signal points is shown in Figure 3. The 64 signal points ("○" in Figure 3) of 64QAM (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64,-w 64 )、(7w 64 ,-3w 64 )、(7w 64 ,―5w 64 )、(7w 64 ,―7w 64 ) (5w 64 ,7w 64 )、(5w 64 ,5w 64 )、(5w 64 ,3w 64 )、(5w 64 ,w 64 )、(5w 64 ,-w 64 )、(5w 64 ,-3w 64 )、(5w 64 ,―5w 64 )、(5w 64 ,―7w 64 ) (3w 64 ,7w 64 )、(3w 64 ,5w 64 )、(3w 64 ,3w 64 )、(3w 64 ,w 64 )、(3w 64 ,-w 64 )、(3w 64 ,-3w 64 )、(3w 64 ,―5w 64 )、(3w 64 ,―7w 64 ) (w 64 ,7w 64 )、(w 64 ,5w 64 )、(w 64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64 ,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w 64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w 64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64 )、(-7w 64 ,w64 ), (-7w 64 ,-w 64 ), (-7w 64 ,-3w 64 ), (-7w 64 ,―5w 64 ), (-7w 64 ,―7w 64 ), the set of b0, b1, b2, b3, b4, and b5 values ​​000000 to 111111 are shown directly below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") directly above the set of b0, b1, b2, b3, b4, and b5 000000 to 111111 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the signal point coordinates in the case of 64QAM is not limited to that shown in FIG. 3. The complex representation of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) becomes the baseband signal (s1(t) or s2(t)).

[0053] The mapping method for 256QAM will now be described. Figure 4 shows an example of a 256QAM signal point arrangement on the in-phase I-quadrature Q plane. In Figure 4, the 256 circles represent 256QAM signal points. The coordinates of the 256 signal points of 256QAM (the "circles" in Figure 4 are signal points) on the in-phase I-quadrature Q plane are as follows: (15w 256 ,15w 256 ), (15w 256 ,13w 256 ), (15w 256 ,11w 256 ), (15w 256 ,9w 256 ), (15w 256 ,7w 256 ), (15w 256 ,5w 256 ), (15w 256 ,3w 256 ), (15w 256 ,w 256 ), (15w 256 ,―15w 256 ), (15w256 ,―13w 256 )、(15w 256 ,―11w 256 )、(15w 256 ,―9w 256 )、(15w 256 ,―7w 256 )、(15w 256 ,―5w 256 )、(15w 256 ,―3w 256 )、(15w 256 ,-In 256 )、 (13in 256 ,15in 256 )、(13w 256 ,13w 256 )、(13w 256 ,11in 256 )、(13w 256 ,9w 256 )、(13w 256 ,7w 256 )、(13w 256 ,5w 256 )、(13w 256 ,3in 256 )、(13w 256 ,In 256 )、 (13in 256 ,―15w 256 )、(13w 256 ,―13w 256 )、(13w 256 ,―11w 256 )、(13w 256 ,―9w 256 )、(13w 256 ,―7w 256 )、(13w 256 ,―5w 256 )、(13w 256 ,―3w 256 )、(13w 256 ,-In 256 )、 (11in 256 ,15in 256 )、(11w 256 ,13w 256 )、(11w 256 ,11in 256 )、(11w256 ,9w 256 )、(11w 256 ,7w 256 )、(11w 256 ,5w 256 )、(11w 256 ,3in 256 )、(11w 256 ,In 256 )、 (11in 256 ,―15w 256 )、(11w 256 ,―13w 256 )、(11w 256 ,―11w 256 )、(11w 256 ,―9w 256 )、(11w 256 ,―7w 256 )、(11w 256 ,―5w 256 )、(11w 256 ,―3w 256 )、(11w 256 ,-In 256 )、 (9in 256 ,15in 256 )、(9w 256 ,13w 256 )、(9w 256 ,11in 256 )、(9w 256 ,9w 256 )、(9w 256 ,7w 256 )、(9w 256 ,5w 256 )、(9w 256 ,3in 256 )、(9w 256 ,In 256 )、 (9in 256 ,―15w 256 )、(9w 256 ,―13w 256 )、(9w 256 ,―11w 256 )、(9w 256 ,―9w 256 )、(9w 256 ,―7w 256 )、(9w 256 ,―5w 256 )、(9w256 ,―3w 256 )、(9w 256 ,-In 256 )、 (7in 256 ,15in 256 )、(7w 256 ,13w 256 )、(7w 256 ,11in 256 )、(7w 256 ,9w 256 )、(7w 256 ,7w 256 )、(7w 256 ,5w 256 )、(7w 256 ,3in 256 )、(7w 256 ,In 256 )、 (7in 256 ,―15w 256 )、(7w 256 ,―13w 256 )、(7w 256 ,―11w 256 )、(7w 256 ,―9w 256 )、(7w 256 ,―7w 256 )、(7w 256 ,―5w 256 )、(7w 256 ,―3w 256 )、(7w 256 ,-In 256 )、 (5in 256 ,15in 256 )、(5in 256 ,13w 256 )、(5in 256 ,11in 256 )、(5in 256 ,9w 256 )、(5in 256 ,7w 256 )、(5in 256 ,5w 256 )、(5in 256 ,3in 256 )、(5in 256 ,In 256 )、 (5in 256 ,―15w256 )、(5w 256 ,―13w 256 )、(5w 256 ,―11w 256 )、(5w 256 ,―9w 256 )、(5w 256 ,―7w 256 )、(5w 256 ,―5w 256 )、(5w 256 ,―3w 256 )、(5w 256 ,―w 256 )、 (3w 256 15w 256 )、(3w 256 ,13w 256 )、(3w 256 ,11w 256 )、(3w 256 ,9w 256 )、(3w 256 ,7w 256 )、(3w 256 ,5w 256 )、(3w 256 ,3w 256 )、(3w 256 ,w 256 )、 (3w 256 ,―15w 256 )、(3w 256 ,―13w 256 )、(3w 256 ,―11w 256 )、(3w 256 ,―9w 256 )、(3w 256 ,―7w 256 )、(3w 256 ,―5w 256 )、(3w 256 ,―3w 256 )、(3w 256 ,―w 256 )、 (w 256 15w 256 )、(w 256 ,13w 256 )、(w 256 ,11w 256 )、(w 256 ,9w256 ),(In 256 ,7w 256 ),(In 256 ,5w 256 ),(In 256 ,3in 256 ),(In 256 ,In 256 )、 (In 256 ,―15w 256 ),(In 256 ,―13w 256 ),(In 256 ,―11w 256 ),(In 256 ,―9w 256 ),(In 256 ,―7w 256 ),(In 256 ,―5w 256 ),(In 256 ,―3w 256 ),(In 256 ,-In 256 )、 (-15w 256 ,15in 256 )、(-15w 256 ,13w 256 )、(-15w 256 ,11in 256 )、(-15w 256 ,9w 256 )、(-15w 256 ,7w 256 )、(-15w 256 ,5w 256 )、(-15w 256 ,3in 256 )、(-15w 256 ,In 256 )、 (-15w 256 ,―15w 256 )、(-15w 256 ,―13w 256 )、(-15w 256 ,―11w 256 )、(-15w 256 ,―9w 256 )、(-15w 256 ,―7w 256 )、(-15w 256 ,―5w 256)、(-15w 256 ,―3w 256 )、(-15w 256 ,-In 256 )、 (-13w 256 ,15in 256 )、(-13w 256 ,13w 256 )、(-13w 256 ,11in 256 )、(-13w 256 ,9w 256 )、(-13w 256 ,7w 256 )、(-13w 256 ,5w 256 )、(-13w 256 ,3in 256 )、(-13w 256 ,In 256 )、 (-13w 256 ,―15w 256 )、(-13w 256 ,―13w 256 )、(-13w 256 ,―11w 256 )、(-13w 256 ,―9w 256 )、(-13w 256 ,―7w 256 )、(-13w 256 ,―5w 256 )、(-13w 256 ,―3w 256 )、(-13w 256 ,-In 256 )、 (-11w 256 ,15in 256 )、(-11w 256 ,13w 256 )、(-11w 256 ,11in 256 )、(-11w 256 ,9w 256 )、(-11w 256 ,7w 256 )、(-11w 256 ,5w 256 )、(-11w 256 ,3in 256 )、(-11w 256,In 256 )、 (-11w 256 ,―15w 256 )、(-11w 256 ,―13w 256 )、(-11w 256 ,―11w 256 )、(-11w 256 ,―9w 256 )、(-11w 256 ,―7w 256 )、(-11w 256 ,―5w 256 )、(-11w 256 ,―3w 256 )、(-11w 256 ,-In 256 )、 (-9w 256 ,15in 256 )、(-9w 256 ,13w 256 )、(-9w 256 ,11in 256 )、(-9w 256 ,9w 256 )、(-9w 256 ,7w 256 )、(-9w 256 ,5w 256 )、(-9w 256 ,3in 256 )、(-9w 256 ,In 256 )、 (-9w 256 ,―15w 256 )、(-9w 256 ,―13w 256 )、(-9w 256 ,―11w 256 )、(-9w 256 ,―9w 256 )、(-9w 256 ,―7w 256 )、(-9w 256 ,―5w 256 )、(-9w 256 ,―3w 256 )、(-9w 256 ,-In 256 )、 (-7w 256 ,15in 256)、(-7w 256 ,13w 256 )、(-7w 256 ,11in 256 )、(-7w 256 ,9w 256 )、(-7w 256 ,7w 256 )、(-7w 256 ,5w 256 )、(-7w 256 ,3in 256 )、(-7w 256 ,In 256 )、 (-7w 256 ,―15w 256 )、(-7w 256 ,―13w 256 )、(-7w 256 ,―11w 256 )、(-7w 256 ,―9w 256 )、(-7w 256 ,―7w 256 )、(-7w 256 ,―5w 256 )、(-7w 256 ,―3w 256 )、(-7w 256 ,-In 256 )、 (-5w 256 ,15in 256 )、(-5w 256 ,13w 256 )、(-5w 256 ,11in 256 )、(-5w 256 ,9w 256 )、(-5w 256 ,7w 256 )、(-5w 256 ,5w 256 )、(-5w 256 ,3in 256 )、(-5w 256 ,In 256 )、 (-5w 256 ,―15w 256 )、(-5w 256 ,―13w 256 )、(-5w 256 ,―11w 256 )、(-5w256 ,―9w 256 )、(-5w 256 ,―7w 256 )、(-5w 256 ,―5w 256 )、(-5w 256 ,―3w 256 )、(-5w 256 ,―w 256 )、 (-3w 256 15w 256 )、(-3w 256 ,13w 256 )、(-3w 256 ,11w 256 )、(-3w 256 ,9w 256 )、(-3w 256 ,7w 256 )、(-3w 256 ,5w 256 )、(-3w 256 ,3w 256 )、(-3w 256 ,w 256 )、 (-3w 256 ,―15w 256 )、(-3w 256 ,―13w 256 )、(-3w 256 ,―11w 256 )、(-3w 256 ,―9w 256 )、(-3w 256 ,―7w 256 )、(-3w 256 ,―5w 256 )、(-3w 256 ,―3w 256 )、(-3w 256 ,―w 256 )、 (-w 256 15w 256 )、(-w 256 ,13w 256 )、(-w 256 ,11w 256 )、(-w 256 ,9w 256 )、(-w 256 ,7w 256 )、(-w 256,5w 256 ), (-w 256 ,3w 256 ), (-w 256 ,w 256 ), (-w 256 ,―15w 256 ), (-w 256 ,―13w 256 ), (-w 256 ,―11w 256 ), (-w 256 ,―9w 256 ), (-w 256 ,―7w 256 ), (-w 256 ,―5w 256 ), (-w 256 ,―3w 256 ), (-w 256 ,―w 256 ), , and (w 256 is a real number greater than 0.

[0054] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, b5, b6, and b7. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), they are mapped to signal point 401 in FIG. 4. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (15w 256 ,15w 256 )

[0055] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the bits to be transmitted (b0, b1, b2, b3, b4, b5, b6, b7). An example of the relationship between the set of b0, b1, b2, b3, b4, b5, b6, b7 (00000000 to 11111111) and the coordinates of the signal points is shown in Figure 4. The 256 signal points of 256QAM (the "circles" in Figure 4) (15w 256 ,15w 256 ), (15w 256 ,13w 256 ), (15w256 ,11in 256 )、(15w 256 ,9w 256 )、(15w 256 ,7w 256 )、(15w 256 ,5w 256 )、(15w 256 ,3in 256 )、(15w 256 ,In 256 )、 (15in 256 ,―15w 256 )、(15w 256 ,―13w 256 )、(15w 256 ,―11w 256 )、(15w 256 ,―9w 256 )、(15w 256 ,―7w 256 )、(15w 256 ,―5w 256 )、(15w 256 ,―3w 256 )、(15w 256 ,-In 256 )、 (13in 256 ,15in 256 )、(13w 256 ,13w 256 )、(13w 256 ,11in 256 )、(13w 256 ,9w 256 )、(13w 256 ,7w 256 )、(13w 256 ,5w 256 )、(13w 256 ,3in 256 )、(13w 256 ,In 256 )、 (13in 256 ,―15w 256 )、(13w 256 ,―13w 256 )、(13w 256 ,―11w 256 )、(13w 256 ,―9w 256 )、(13w 256 ,―7w256 )、(13w 256 ,―5w 256 )、(13w 256 ,―3w 256 )、(13w 256 ,-In 256 )、 (11in 256 ,15in 256 )、(11w 256 ,13w 256 )、(11w 256 ,11in 256 )、(11w 256 ,9w 256 )、(11w 256 ,7w 256 )、(11w 256 ,5w 256 )、(11w 256 ,3in 256 )、(11w 256 ,In 256 )、 (11in 256 ,―15w 256 )、(11w 256 ,―13w 256 )、(11w 256 ,―11w 256 )、(11w 256 ,―9w 256 )、(11w 256 ,―7w 256 )、(11w 256 ,―5w 256 )、(11w 256 ,―3w 256 )、(11w 256 ,-In 256 )、 (9in 256 ,15in 256 )、(9w 256 ,13w 256 )、(9w 256 ,11in 256 )、(9w 256 ,9w 256 )、(9w 256 ,7w 256 )、(9w 256 ,5w 256 )、(9w 256 ,3in 256 )、(9w256 ,In 256 )、 (9in 256 ,―15w 256 )、(9w 256 ,―13w 256 )、(9w 256 ,―11w 256 )、(9w 256 ,―9w 256 )、(9w 256 ,―7w 256 )、(9w 256 ,―5w 256 )、(9w 256 ,―3w 256 )、(9w 256 ,-In 256 )、 (7in 256 ,15in 256 )、(7w 256 ,13w 256 )、(7w 256 ,11in 256 )、(7w 256 ,9w 256 )、(7w 256 ,7w 256 )、(7w 256 ,5w 256 )、(7w 256 ,3in 256 )、(7w 256 ,In 256 )、 (7in 256 ,―15w 256 )、(7w 256 ,―13w 256 )、(7w 256 ,―11w 256 )、(7w 256 ,―9w 256 )、(7w 256 ,―7w 256 )、(7w 256 ,―5w 256 )、(7w 256 ,―3w 256 )、(7w 256 ,-In 256 )、 (5in 256 ,15in 256 )、(5in 256 ,13w256 )、(5w 256 ,11w 256 )、(5w 256 ,9w 256 )、(5w 256 ,7w 256 )、(5w 256 ,5w 256 )、(5w 256 ,3w 256 )、(5w 256 ,w 256 )、 (5w 256 ,―15w 256 )、(5w 256 ,―13w 256 )、(5w 256 ,―11w 256 )、(5w 256 ,―9w 256 )、(5w 256 ,―7w 256 )、(5w 256 ,―5w 256 )、(5w 256 ,―3w 256 )、(5w 256 ,―w 256 )、 (3w 256 15w 256 )、(3w 256 ,13w 256 )、(3w 256 ,11w 256 )、(3w 256 ,9w 256 )、(3w 256 ,7w 256 )、(3w 256 ,5w 256 )、(3w 256 ,3w 256 )、(3w 256 ,w 256 )、 (3w 256 ,―15w 256 )、(3w 256 ,―13w 256 )、(3w 256 ,―11w 256 )、(3w 256 ,―9w 256 )、(3w 256 ,―7w 256)、(3in 256 ,―5w 256 )、(3in 256 ,―3w 256 )、(3in 256 ,-In 256 )、 (In 256 ,15in 256 ),(In 256 ,13w 256 ),(In 256 ,11in 256 ),(In 256 ,9w 256 ),(In 256 ,7w 256 ),(In 256 ,5w 256 ),(In 256 ,3in 256 ),(In 256 ,In 256 )、 (In 256 ,―15w 256 ),(In 256 ,―13w 256 ),(In 256 ,―11w 256 ),(In 256 ,―9w 256 ),(In 256 ,―7w 256 ),(In 256 ,―5w 256 ),(In 256 ,―3w 256 ),(In 256 ,-In 256 )、 (-15w 256 ,15in 256 )、(-15w 256 ,13w 256 )、(-15w 256 ,11in 256 )、(-15w 256 ,9w 256 )、(-15w 256 ,7w 256 )、(-15w 256 ,5w 256 )、(-15w 256 ,3in 256 )、(-15w 256 ,In 256 )、 (-15w 256 ,―15w 256 )、(-15w 256 ,―13w 256 )、(-15w 256 ,―11w 256 )、(-15w 256 ,―9w 256 )、(-15w 256 ,―7w 256 )、(-15w 256 ,―5w 256 )、(-15w 256 ,―3w 256 )、(-15w 256 ,-In 256 )、 (-13w 256 ,15in 256 )、(-13w 256 ,13w 256 )、(-13w 256 ,11in 256 )、(-13w 256 ,9w 256 )、(-13w 256 ,7w 256 )、(-13w 256 ,5w 256 )、(-13w 256 ,3in 256 )、(-13w 256 ,In 256 )、 (-13w 256 ,―15w 256 )、(-13w 256 ,―13w 256 )、(-13w 256 ,―11w 256 )、(-13w 256 ,―9w 256 )、(-13w 256 ,―7w 256 )、(-13w 256 ,―5w 256 )、(-13w 256 ,―3w 256 )、(-13w 256 ,-In 256 )、 (-11w 256 ,15in 256)、(-11w 256 ,13w 256 )、(-11w 256 ,11in 256 )、(-11w 256 ,9w 256 )、(-11w 256 ,7w 256 )、(-11w 256 ,5w 256 )、(-11w 256 ,3in 256 )、(-11w 256 ,In 256 )、 (-11w 256 ,―15w 256 )、(-11w 256 ,―13w 256 )、(-11w 256 ,―11w 256 )、(-11w 256 ,―9w 256 )、(-11w 256 ,―7w 256 )、(-11w 256 ,―5w 256 )、(-11w 256 ,―3w 256 )、(-11w 256 ,-In 256 )、 (-9w 256 ,15in 256 )、(-9w 256 ,13w 256 )、(-9w 256 ,11in 256 )、(-9w 256 ,9w 256 )、(-9w 256 ,7w 256 )、(-9w 256 ,5w 256 )、(-9w 256 ,3in 256 )、(-9w 256 ,In 256 )、 (-9w 256 ,―15w 256 )、(-9w 256 ,―13w 256 )、(-9w 256 ,―11w 256)、(-9w 256 ,―9w 256 )、(-9w 256 ,―7w 256 )、(-9w 256 ,―5w 256 )、(-9w 256 ,―3w 256 )、(-9w 256 ,―w 256 )、 (-7w 256 15w 256 )、(-7w 256 ,13w 256 )、(-7w 256 ,11w 256 )、(-7w 256 ,9w 256 )、(-7w 256 ,7w 256 )、(-7w 256 ,5w 256 )、(-7w 256 ,3w 256 )、(-7w 256 ,w 256 )、 (-7w 256 ,―15w 256 )、(-7w 256 ,―13w 256 )、(-7w 256 ,―11w 256 )、(-7w 256 ,―9w 256 )、(-7w 256 ,―7w 256 )、(-7w 256 ,―5w 256 )、(-7w 256 ,―3w 256 )、(-7w 256 ,―w 256 )、 (-5w 256 15w 256 )、(-5w 256 ,13w 256 )、(-5w 256 ,11w 256 )、(-5w 256 ,9w 256 )、(-5w 256 ,7w 256 )、(-5w256 ,5w 256 )、(-5w 256 ,3w 256 )、(-5w 256 ,w 256 )、 (-5w 256 ,―15w 256 )、(-5w 256 ,―13w 256 )、(-5w 256 ,―11w 256 )、(-5w 256 ,―9w 256 )、(-5w 256 ,―7w 256 )、(-5w 256 ,―5w 256 )、(-5w 256 ,―3w 256 )、(-5w 256 ,―w 256 )、 (-3w 256 15w 256 )、(-3w 256 ,13w 256 )、(-3w 256 ,11w 256 )、(-3w 256 ,9w 256 )、(-3w 256 ,7w 256 )、(-3w 256 ,5w 256 )、(-3w 256 ,3w 256 )、(-3w 256 ,w 256 )、 (-3w 256 ,―15w 256 )、(-3w 256 ,―13w 256 )、(-3w 256 ,―11w 256 )、(-3w 256 ,―9w 256 )、(-3w 256 ,―7w 256 )、(-3w 256 ,―5w 256 )、(-3w 256 ,―3w 256 )、(-3w 256 ,―w256 ), (-w 256 ,15w 256 ), (-w 256 ,13w 256 ), (-w 256 ,11w 256 ), (-w 256 ,9w 256 ), (-w 256 ,7w 256 ), (-w 256 ,5w 256 ), (-w 256 ,3w 256 ), (-w 256 ,w 256 ), (-w 256 ,―15w 256 ), (-w 256 ,―13w 256 ), (-w 256 ,―11w 256 ), (-w 256 ,―9w 256 ), (-w 256 ,―7w 256 ), (-w 256 ,―5w 256 ), (-w 256 ,―3w 256 ), (-w 256 ,―w 256 ), The values ​​of the set 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, and b7 are shown directly below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") directly above the set 00000000 to 11111111 of b0, b1, b2, b3, b4, b5, b6, and b7 become the in-phase component I and quadrature component Q of the mapped baseband signal. Note that the relationship between the set of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points in the case of 256QAM is not limited to that shown in Fig. 4. The complex representation of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 256QAM) becomes the baseband signal (s1(t) or s2(t)).

[0056] In this case, it is common to make the average power of baseband signal 505A (s1(t)(s1(i))) output by mapping unit 504 in FIGS. 5 to 7 equal to the average power of baseband signal 505B (s2(t)(s2(i))). Therefore, the coefficient w q , the coefficient w described in the 16QAM mapping method explained above 16 , the coefficient w described in the 64QAM mapping method explained above 64 And the coefficient w described in the 256QAM mapping method described above 256 The following relation holds true:

[0057]

number

[0058]

number

[0059]

number

[0060]

number

[0061] In the DVB standard, when modulated signal #1 and modulated signal #2 are transmitted from two antennas in a MIMO transmission method, there are cases where the transmission average power of modulated signal #1 and the transmission average power of modulated signal #2 are set to be different. As an example, in the above-mentioned cases of equations (R2), (R3), (R4), (R5), and (R8), Q1≠Q2 occurs. As a more specific example, consider the following.

[0062] <1> In equation (R2), when the precoding matrix F (or F(i)) is expressed by one of the following equations:

[0063]

number

[0064] or

[0065]

number

[0066] or

[0067]

number

[0068] or

[0069]

number

[0070] or

[0071]

number

[0072] or

[0073]

number

[0074] or

[0075]

number

[0076] or

[0077]

number

[0078] In formulas (R15), (R16), (R17), (R18), (R19), (R20), (R21), and (R22), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). or

[0079]

number

[0080] or

[0081]

number

[0082] or

[0083]

number

[0084] or

[0085]

number

[0086] or

[0087]

number

[0088] or

[0089]

number

[0090] or

[0091]

number

[0092] or

[0093]

number

[0094] In the formulas (R23), (R25), (R27), and (R29), β may be a real number or an imaginary number, provided that β is not 0 (zero). or

[0095]

number

[0096] or

[0097]

number

[0098] or

[0099]

number

[0100] or

[0101]

number

[0102] However, θ 11 (i), θ 21 (i) is a function of i (of time or frequency), λ is a fixed value, α can be real or imaginary, and β can be real or imaginary, provided that α is not 0 (zero), and β is not 0 (zero). <2> In equation (R3), the precoding matrix F (or F(i)) is expressed by any one of equations (15) to (30). <3> In equation (R4), the precoding matrix F (or F(i)) is expressed by any one of equations (15) to (30). <4> In equation (R5), the precoding matrix F (or F(i)) is expressed by any one of equations (15) to (34). <5> In equation (R8), the precoding matrix F (or F(i)) is expressed by any one of equations (15) to (30).

[0103] Also, <1> from <5> In this case, the modulation method of s1(t) and the modulation method of s2(t) (the modulation method of s1(i) and the modulation method of s2(i)) are different. The important points of this configuration example have been explained above. The points explained below are as follows: <1> from <5> This is particularly important when using a precoding method in <1> from <5> In the preceding method in the above, it is also possible to implement the method when a preceding matrix other than those in equations (15) to (34) is used.

[0104] <1> from <5> The modulation level of the modulation scheme of s1(t) (s1(i)) (i.e., baseband signal 505A) in g(g is an integer greater than or equal to 1), <1> from <5> The modulation level of the modulation method of s2(t) (s2(i)) (that is, baseband signal 505B) in h (h is an integer greater than or equal to 1) (Note that g≠h.) Then, one symbol of s1(t)(s1(i)) transmits g bits of data, and one symbol of s2(t)(s2(i)) transmits h bits of data. Therefore, one slot formed by one symbol of s1(t)(s1(i)) and one symbol of s2(t)(s2(i)) transmits g+h bits. In this case, the following condition is important to obtain a high spatial diversity gain.

[0105] <Condition R-1> When precoding (including processes other than precoding) according to formula (R2), formula (R3), formula (R4), formula (R5), or formula (R8) is performed, the number of candidate signal points in one symbol of signal z1(t) (z1(i)) after processing such as precoding is 2 in the in-phase I-quadrature Q plane. g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, in one symbol of the signal z2(t)(z2(i)) after processing such as precoding, the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) Next, we will express <Condition R-1> differently and explain the additional conditions separately for formula (R2), formula (R3), formula (R4), formula (R5), and formula (R8).

[0106] (Case 1) When a fixed precoding matrix is ​​used and equation (R2) is processed: Consider the following equation as an intermediate step in the calculation of equation (R2).

[0107]

number

[0108] (In Case 1, the precoding matrix F is a fixed precoding matrix. (However, if the modulation scheme for s1(t)(s1(i)) and / or the modulation scheme for s2(t)(s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0109] In this case, if the following conditions are met, a high spatial diversity gain can be obtained. <Condition R-2> In one symbol of the signal u1(t)(u1(i)) in equation (R35), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R35), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, in equation (R2), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), consider the following condition.

[0110] <Condition R-3> In one symbol of the signal u1(t)(u1(i)) in equation (R35), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D1 (where D1 is a real number greater than or equal to 0 (zero) (D1 ≥ 0). When D1 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0111] In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R35), the number of candidate signal points on the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+hThe minimum Euclidean distance between the candidate signal points is D2 (where D2 is a real number greater than or equal to 0 (zero) (D2 ≥ 0). When D2 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0112] In this case, D1>D2 (D1 is greater than D2) holds true. Incidentally, Figure 53 shows the relationship between transmitting antennas and receiving antennas. Assume that modulated signal #1 (5301A) is transmitted from transmitting antenna #1 (5302A) of the transmitting device, and modulated signal #2 (5301B) is transmitted from transmitting antenna #2 (5302B). At this time, it is assumed that z1(t) (z1(i)) (i.e., u1(t) (u1(i))) is transmitted from transmitting antenna #1 (5302A), and z2(t) (z2(i)) (i.e., u2(t) (u2(i))) is transmitted from transmitting antenna #2 (5302B). Then, the receiving antenna #1 (5303X) and receiving antenna #2 (5303Y) of the receiving device receive the modulated signal transmitted by the transmitting device (receiving a receiving signal 530X and a receiving signal 5304Y). At this time, the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302A) is calculated as h 11 (t), and the propagation coefficient from transmitting antenna #1 (5302A) to receiving antenna #2 (5303Y) is h 21 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #1 (5303X) is h 12 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #2 (5303Y) is h 22 Let (t) be the time. (t is time) In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-3>, the receiving device is more likely to be able to obtain high data reception quality. For the same reason, when |Q1| < |Q2|, <Condition R-3'> may be satisfied.

[0113] <Condition R-3'> In one symbol of the signal u1(t) (u1(i)) of Equation (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of the g + h-bit data, when signal points are created in the in-phase I - quadrature Q plane, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u1(t) (u1(i)), let the minimum Euclidean distance be D1 (note that D1 is a real number greater than or equal to 0 (D1 ≥ 0). When D1 is 0 (zero), among the 2 g+h signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0114] Also, in one symbol of the signal u2(t) (u2(i)) of Equation (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of the g + h-bit data, when signal points are created in the in-phase I - quadrature Q plane, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u2(t) (u2(i)), let the minimum Euclidean distance be D2 (note that D2 is a real number greater than or equal to 0 (D2 ≥ 0). When D2 is 0 (zero), among the 2 g+h signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0115] At this time, D1 < D2 (D1 is smaller than D2) holds. In Case 1, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0116] (Case 2) When using any of the precoding matrices in equations (R15) to (R30) and processing equation (R2): Consider equation (R35) as an intermediate equation in the calculation of equation (R2). In Case 2, the precoding matrix F is a fixed precoding matrix, and is expressed by any of equations (R15) to (R30). (However, if the modulation scheme for s1(t) (s1(i)) and / or the modulation scheme for s2(t) (s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h. In this case, if <Condition R-2> is met, a high spatial diversity gain can be obtained.

[0117] Then, in equation (R2), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), consider that <Condition R-3> is satisfied, just as in Case 1. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-3>, the receiving device is more likely to be able to obtain high data reception quality. Furthermore, even if the following conditions are met, the receiving device is more likely to be able to obtain high data reception quality. <Condition R-3''> <Condition R-3> is met, and in formula (R2), P1=P2 is met.

[0118] In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-3''>, the receiving device is more likely to be able to obtain high data reception quality.

[0119] For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-3'> is satisfied. For the same reason, when |Q1|<|Q2|, even if the following condition is met, the receiving device is more likely to be able to obtain high data reception quality. <Condition R-3'''> <Condition R-3'> is satisfied, and in formula (R2), P1=P2 is satisfied.

[0120] In Case 2, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used. (Case 3) When performing the process of Equation (R2) using any of the precoding matrices from Equation (R31) to Equation (R34): As an intermediate equation of the operation of Equation (R2), consider Equation (R35). In the case of Case 3, assume that the precoding matrix F switches the precoding matrix depending on time (or frequency). And the precoding matrix F(F(i)) is expressed by any of Equation (R31) to Equation (R34). The modulation order of s1(t)(s1(i)) (that is, the baseband signal 505A) is 2 g (where g is an integer greater than or equal to 1), the modulation order of s2(t)(s2(i)) (that is, the baseband signal 505B) is 2 h (where h is an integer greater than or equal to 1), and g≠h.

[0121] At this time, when the following <Condition R-4> is satisfied, a high spatial diversity gain can be obtained. <Condition R-4>· When the symbol number i is between N and M (where N is an integer, M is an integer, and N<M (M is smaller than N)), assume that the modulation method of s1(t)(s1(i)) (that is, the baseband signal 505A) is fixed (does not switch), and the modulation method of s2(t)(s2(i)) (that is, the baseband signal 505B) is fixed (does not switch). And when the symbol number i is between N and M, for all i that satisfy this, in one symbol of the signal u1(t)(u1(i)) of Equation (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (When signal points are created in the in-phase I - quadrature Q plane for all possible values of g + h-bit data in one symbol, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) In addition, when the symbol number i is N or more and M or less, for all i that satisfy this condition, in one symbol of the signal u2(t) (u2(i)) of the formula (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, if signal points are created in the in-phase I - quadrature Q plane for all possible values of the g + h-bit data, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the formula (R2), when |Q1| > |Q2| (the absolute value of Q1 is larger than the absolute value of Q2), consider that <Condition R - 5> holds.

[0122] <Condition R - 5> When the symbol number i is N or more and M or less (N is an integer, M is an integer, and N < M (M is smaller than N)), assume that the modulation method of s1(t) (s1(i)) (that is, the baseband signal 505A) is fixed (does not change), and the modulation method of s2(t) (s2(i)) (that is, the baseband signal 505B) is fixed (does not change).

[0123] When the symbol number i is N or more and M or less, for all i that satisfy this condition, in one symbol of the signal u1(t) (u1(i)) of the formula (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, if signal points are created in the in-phase I - quadrature Q plane for all possible values of the g + h-bit data, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And at symbol number i, in the in-phase I - quadrature Q plane, let the minimum Euclidean distance of the 2 g+h pieces of candidate signal points of u1(t) (u1(i)) be D1(i) (note that D1(i) is a real number of 0 (zero) or more (D1(i) ≥ 0). When D1(i) is 0 (zero), 2 g+hOf these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0124] In addition, when the symbol number i is between N and M, for all i that satisfy this, the number of candidate signal points in one symbol of the signal u2(t)(u2(i)) in equation (R35) on the in-phase I-quadrature Q plane is 2. g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, for symbol number i, the 2nd of u2(t)(u2(i)) in the in-phase I-quadrature Q plane is g+h The minimum Euclidean distance between the candidate signal points is defined as D2(i). (Note that D2(i) is a real number greater than or equal to 0 (D2(i) ≥ 0). When D2(i) is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0125] In this case, when the symbol number i is between N and M, D1(i)>D2(i) (D1(i) is greater than D2(i)) holds for all i that satisfy this. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-5>, the receiving device is more likely to be able to obtain high data reception quality. Furthermore, even if the following conditions are met, the receiving device is more likely to be able to obtain high data reception quality.

[0126] <Condition R-5'> <Condition R-5> is met, and in formula (R2), P1=P2 is met. At this time, since |Q1| > |Q2| holds, the reception state of the modulation signal of z1(t)(z1(i)) (that is, u1(t)(u1(i))) may be a dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-5'>, it is highly likely that the receiving device can obtain high reception quality of data.

[0127] For the same reason, when |Q1| < |Q2|, <Condition R-5''> may hold. <Condition R-5''> When the symbol number i is N or more and M or less (where N is an integer, M is an integer, and N < M (M is smaller than N)), assume that the modulation method of s1(t)(s1(i)) (that is, the baseband signal 505A) is fixed (does not change), and the modulation method of s2(t)(s2(i)) (that is, the baseband signal 505B) is fixed (does not change).

[0128] When the symbol number i is N or more and M or less, for all i that satisfy this, in one symbol of the signal u1(t)(u1(i)) of Equation (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (When signal points are created in the in-phase I - quadrature Q plane for all possible values of g + h-bit data in one symbol, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And at symbol number i, in the in-phase I - quadrature Q plane, let the minimum Euclidean distance of the 2 g+h pieces of candidate signal points of u1(t)(u1(i)) be D1(i) (note that D1(i) is a real number of 0 (zero) or more (D1(i) ≥ 0). When D1(i) is 0 (zero), among the 2 g+h pieces of signal points, there are signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0129] Also, when the symbol number i is N or more and M or less, for all i that satisfy this condition, in one symbol of the signal u2(t) (u2(i)) of the formula (R35), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, if signal points are created in the in-phase I - quadrature Q plane for all possible values of g + h - bit data, 2 g+h pieces of signal points can be created. This number becomes the number of candidate signal points.) And at symbol number i, in the in-phase I - quadrature Q plane, let the minimum Euclidean distance of the 2 g+h candidate signal points of u2(t) (u2(i)) be D2(i) (note that D2(i) is a real number of 0 (zero) or more (D2(i) ≧ 0). When D2(i) is 0 (zero), among the 2 g+h pieces of signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0130] At this time, when the symbol number i is N or more and M or less, for all i that satisfy this condition, D1(i) < D2(i) (D1(i) is smaller than D2(i)) holds. Also, for the same reason, when |Q1| < |Q2|, even if the following conditions are satisfied, the receiver is likely to obtain high - quality received data. <Condition R - 5’’’> <Condition R - 5’’> holds and in the formula (R2), P1 = P2 holds.

[0131] In Case 3, for example, as the modulation method in s1(t) (s1(i)) and the modulation method in s2(t) (s2(i)), as described above, QPSK, 16QAM, 64QAM, 256QAM will be applied. At this time, for the specific mapping method, it will be as described above in this configuration example. However, modulation methods other than QPSK, 16QAM, 64QAM, 256QAM may also be used.

[0132] (Case 4) When a fixed precoding matrix is ​​used and equation (R3) is processed: Consider the following equation as an intermediate step in the calculation of equation (R3).

[0133]

number

[0134] (In Case 4, the precoding matrix F is a fixed precoding matrix. (However, if the modulation scheme for s1(t)(s1(i)) and / or the modulation scheme for s2(t)(s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0135] In this case, if the following conditions are met, a high spatial diversity gain can be obtained. <Condition R-6> In one symbol of the signal u1(t)(u1(i)) in equation (R36), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R36), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h(In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, in equation (R3), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), consider the following condition.

[0136] <Condition R-7> In one symbol of the signal u1(t)(u1(i)) in equation (R36), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D1 (where D1 is a real number greater than or equal to 0 (zero) (D1 ≥ 0). When D1 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0137] In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R36), the number of candidate signal points on the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D2 (where D2 is a real number greater than or equal to 0 (zero) (D2 ≥ 0). When D2 is 0 (zero), 2 g+hOf these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0138] In this case, D1>D2 (D1 is greater than D2) holds true. Incidentally, Figure 53 shows the relationship between transmitting antennas and receiving antennas. Assume that modulated signal #1 (5301A) is transmitted from transmitting antenna #1 (5302A) of the transmitting device, and modulated signal #2 (5301B) is transmitted from transmitting antenna #2 (5302B). At this time, it is assumed that z1(t) (z1(i)) (i.e., u1(t) (u1(i))) is transmitted from transmitting antenna #1 (5302A), and z2(t) (z2(i)) (i.e., u2(t) (u2(i))) is transmitted from transmitting antenna #2 (5302B).

[0139] Then, the receiving antenna #1 (5303X) and receiving antenna #2 (5303Y) of the receiving device receive the modulated signal transmitted by the transmitting device (receiving a receiving signal 530X and a receiving signal 5304Y). At this time, the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302A) is calculated as h 11 (t), and the propagation coefficient from transmitting antenna #1 (5302A) to receiving antenna #2 (5303Y) is h 21 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #1 (5303X) is h 12 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #2 (5303Y) is h 22 Let (t) be the time. (t is time) In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-7>, the receiving device is more likely to be able to obtain high data reception quality. For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-7'> is satisfied.

[0140] <Condition R-7’> In one symbol of the signal u1(t) (u1(i)) of Equation (R36), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of the g + h-bit data, when creating signal points in the in-phase I - quadrature Q plane, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u1(t) (u1(i)), let the minimum Euclidean distance be D1 (note that D1 is a real number greater than or equal to 0 (D1≥0). When D1 is 0 (zero), among the 2 g+h signal points, there will be signal points existing at the same position in the in-phase I - quadrature Q plane.).

[0141] Also, in one symbol of the signal u2(t) (u2(i)) of Equation (R36), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of the g + h-bit data, when creating signal points in the in-phase I - quadrature Q plane, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u2(t) (u2(i)), let the minimum Euclidean distance be D2 (note that D2 is a real number greater than or equal to 0 (D2≥0). When D2 is​​​​​​​​In Case 4, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0143] (Case 5) When using any of the precoding matrices in equations (R15) to (R30) and processing equation (R3): Consider equation (R36) as an intermediate equation in the calculation of equation (R3). In Case 5, the precoding matrix F is a fixed precoding matrix, and is expressed by any of equations (R15) to (R30). (However, if the modulation scheme for s1(t) (s1(i)) and / or the modulation scheme for s2(t) (s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h. In this case, if <Condition R-6> is met, a high spatial diversity gain can be obtained.

[0144] Then, in equation (R3), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), consider that <Condition R-7> is satisfied, just as in Case 4. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-7>, the receiving device is more likely to be able to obtain high data reception quality. Furthermore, even if the following conditions are met, the receiving device is more likely to be able to obtain high data reception quality.

[0145] <Condition R-7''> <Condition R-7> is met, and in formula (R3), P1=P2 is met. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-7''>, the receiving device is more likely to be able to obtain high data reception quality.

[0146] For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-7'> is satisfied. For the same reason, when |Q1|<|Q2|, even if the following condition is met, the receiving device is more likely to be able to obtain high data reception quality. <Condition R-7'''> <Condition R-7'> is satisfied, and in formula (R3), P1=P2 is satisfied.

[0147] In Case 5, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0148] (Case 6) When a fixed precoding matrix is ​​used and equation (R4) is processed: Consider the following equation as an intermediate step in the calculation of equation (R4).

[0149]

number

[0150] (In Case 6, the precoding matrix F is a fixed precoding matrix. (However, if the modulation scheme for s1(t)(s1(i)) and / or the modulation scheme for s2(t)(s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0151] In this case, if the following conditions are met, a high spatial diversity gain can be obtained. <Condition R-8> In one symbol of the signal u1(t)(u1(i)) in equation (R37), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R37), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h(In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, in equation (R4), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), the following conditions are considered.

[0152] <Condition R-9> In one symbol of the signal u1(t)(u1(i)) in equation (R37), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D1 (where D1 is a real number greater than or equal to 0 (zero) (D1 ≥ 0). When D1 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0153] In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R37), the number of candidate signal points on the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D2 (where D2 is a real number greater than or equal to 0 (zero) (D2 ≥ 0). When D2 is 0 (zero), 2 g+hOf these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0154] In this case, D1>D2 (D1 is greater than D2) holds true. Incidentally, Figure 53 shows the relationship between transmitting antennas and receiving antennas. Assume that modulated signal #1 (5301A) is transmitted from transmitting antenna #1 (5302A) of the transmitting device, and modulated signal #2 (5301B) is transmitted from transmitting antenna #2 (5302B). At this time, it is assumed that z1(t) (z1(i)) (i.e., u1(t) (u1(i))) is transmitted from transmitting antenna #1 (5302A), and z2(t) (z2(i)) (i.e., u2(t) (u2(i))) is transmitted from transmitting antenna #2 (5302B).

[0155] Then, the receiving antenna #1 (5303X) and receiving antenna #2 (5303Y) of the receiving device receive the modulated signal transmitted by the transmitting device (receiving a receiving signal 530X and a receiving signal 5304Y). At this time, the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302A) is calculated as h 11 (t), and the propagation coefficient from transmitting antenna #1 (5302A) to receiving antenna #2 (5303Y) is h 21 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #1 (5303X) is h 12 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #2 (5303Y) is h 22 Let (t) be the time. (t is time) In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-9>, the receiving device is more likely to be able to obtain high data reception quality.

[0156] For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-9'> is satisfied. <Condition R-9’> In one symbol of the signal u1(t) (u1(i)) of formula (R37), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of g + h bits of data, when signal points are created in the in-phase I - quadrature Q plane, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u1(t) (u1(i)), let the minimum Euclidean distance be D1 (note that D1 is a real number greater than or equal to 0 (D1≥0). When D1 is 0 (zero), among the 2 g+h pieces of signal points, there will be signal points existing at the same position in the in-phase I - quadrature Q plane.).

[0157] Also, in one symbol of the signal u2(t) (u2(i)) of formula (R37), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of g + h bits of data, when signal points are created in the in-phase I - quadrature Q plane, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u2(t) (u2(i)), let the minimum Euclidean distance be D2 (note that D2 is a real number greater than or equal to 0 (D2≥0). When D2 is 0 (zero), among the 2 g+h pieces of signal points, there will be signal points existing at the same position in the in-phase I - quadrature Q plane.). <照抄原文

[0158] <照抄原文 At this time, D1 < D2 (D1 is smaller than D2) holds. In Case 6, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0159] (Case 7) When using any of the precoding matrices in equations (R15) to (R30) and processing equation (R4): Consider equation (R37) as an intermediate equation in the calculation of equation (R4). In Case 7, the precoding matrix F is a fixed precoding matrix, and is expressed by any of equations (R15) to (R30). (However, if the modulation scheme for s1(t) (s1(i)) and / or the modulation scheme for s2(t) (s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h. In this case, if <Condition R-8> is met, a high spatial diversity gain can be obtained.

[0160] Then, in equation (R4), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), we consider that <Condition R-9> is satisfied, just as in Case 6. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-9>, the receiving device is more likely to be able to obtain high data reception quality. Furthermore, even if the following conditions are met, the receiving device is more likely to be able to obtain high data reception quality.

[0161] <Condition R-9''> <Condition R-9> is met, and in equation (R4), P1=P2 is met. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-9''>, the receiving device is more likely to be able to obtain high data reception quality.

[0162] For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-9'> is satisfied. For the same reason, when |Q1|<|Q2|, even if the following condition is met, the receiving device is more likely to be able to obtain high data reception quality. <Condition R-9'''> <Condition R-9'> is satisfied, and in formula (R4), P1=P2 is satisfied.

[0163] In Case 7, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0164] (Case 8) When a fixed precoding matrix is ​​used and equation (R5) is processed: Consider the following equation as an intermediate step in the calculation of equation (R5).

[0165]

number

[0166] (In Case 8, the precoding matrix F is a fixed precoding matrix. (However, if the modulation scheme for s1(t)(s1(i)) and / or the modulation scheme for s2(t)(s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0167] In this case, if the following conditions are met, a high spatial diversity gain can be obtained. <Condition R-10> In one symbol of the signal u1(t)(u1(i)) in equation (R38), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R38), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h(In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, in equation (R5), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), the following conditions are considered.

[0168] <Condition R-11> In one symbol of the signal u1(t)(u1(i)) in equation (R38), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D1 (where D1 is a real number greater than or equal to 0 (zero) (D1 ≥ 0). When D1 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0169] In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R38), the number of candidate signal points on the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D2 (where D2 is a real number greater than or equal to 0 (zero) (D2 ≥ 0). When D2 is 0 (zero), 2 g+hOf these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0170] In this case, D1>D2 (D1 is greater than D2) holds true. Incidentally, Figure 53 shows the relationship between transmitting antennas and receiving antennas. Assume that modulated signal #1 (5301A) is transmitted from transmitting antenna #1 (5302A) of the transmitting device, and modulated signal #2 (5301B) is transmitted from transmitting antenna #2 (5302B). At this time, it is assumed that z1(t) (z1(i)) (i.e., u1(t) (u1(i))) is transmitted from transmitting antenna #1 (5302A), and z2(t) (z2(i)) (i.e., u2(t) (u2(i))) is transmitted from transmitting antenna #2 (5302B). Then, the receiving antenna #1 (5303X) and receiving antenna #2 (5303Y) of the receiving device receive the modulated signal transmitted by the transmitting device (receiving a receiving signal 530X and a receiving signal 5304Y). At this time, the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302A) is calculated as h 11 (t), and the propagation coefficient from transmitting antenna #1 (5302A) to receiving antenna #2 (5303Y) is h 21 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #1 (5303X) is h 12 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #2 (5303Y) is h 22 Let (t) be the time. (t is time) In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-11>, the receiving device is more likely to be able to obtain high data reception quality.

[0171] For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-11'> is satisfied. <Condition R-11’> In one symbol of the signal u1(t) (u1(i)) of Equation (R38), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of g + h bit data, when creating signal points in the in-phase I - quadrature Q plane, g+h 2 signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u1(t) (u1(i)), let the minimum Euclidean distance be D1 (note that D1 is a real number greater than or equal to 0 (D1≥0). When D1 is 0 (zero), g+h among the 2 signal points, there will be signal points existing at the same position in the in-phase I - quadrature Q plane.).

[0172] Also, in one symbol of the signal u2(t) (u2(i)) of Equation (R38), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of g + h bit data, when creating signal points in the in-phase I - quadrature Q plane, g+h 2 signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, for the 2 g+h candidate signal points of u2(t) (u2(i)), let the minimum Euclidean distance be D2 (note that D2 is a real number greater than or equal to 0 (D2≥0). When D2 is 0 (zero), g+h among the 2 signal points, there will be signal points existing at the same position in the in-phase I - quadrature Q plane.).

[0173] At this time, D1 < D2 (D1 is smaller than D2) holds. In Case 8, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0174] (Case 9) When processing equation (R5) using one of the precoding matrices from equation (R15) to equation (R30): Consider equation (R38) as an intermediate equation in the calculation of equation (R5). In Case 9, the precoding matrix F is a fixed precoding matrix, and is expressed by any of equations (R15) to (R30). (However, if the modulation scheme for s1(t) (s1(i)) and / or the modulation scheme for s2(t) (s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0175] In this case, if <Condition R-10> is met, a high spatial diversity gain can be obtained. Then, in equation (R5), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), consider that <Condition R-11> is satisfied, just as in Case 8.

[0176] In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-11>, the receiving device is more likely to be able to obtain high data reception quality. For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-11'> is satisfied.

[0177] In Case 9, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0178] (Case 10) When using any of the precoding matrices in equations (R31) to (R34) and processing equation (R5): Consider equation (R38) as an intermediate equation in the calculation of equation (R5). Note that in Case 10, the precoding matrix F switches depending on time (or frequency). The precoding matrix F(F(i)) is expressed by one of equations (R31) to (R34). The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0179] In this case, if the following <Condition R-12> is met, a high spatial diversity gain can be obtained. <Condition R-12> When the symbol number i is N or more and M or less (N is an integer, M is an integer, and N < M (M is smaller than N)), assume that the modulation method of s1(t) (s1(i)) (that is, the baseband signal 505A) is fixed (does not change), and the modulation method of s2(t) (s2(i)) (that is, the baseband signal 505B) is fixed (does not change). And when the symbol number i is N or more and M or less, for all i that satisfy this, in one symbol of the signal u1(t) (u1(i)) of Equation (R38), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (When creating signal points in the in-phase I - quadrature Q plane for all possible values of g + h - bit data in one symbol, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) In addition, when the symbol number i is N or more and M or less, for all i that satisfy this, in one symbol of the signal u2(t) (u2(i)) of Equation (R38), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (When creating signal points in the in-phase I - quadrature Q plane for all possible values of g + h - bit data in one symbol, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And in Equation (R5), consider that <Condition R - 13> holds when |Q1| > |Q2| (the absolute value of Q1 is greater than the absolute value of Q2).

[0180] <Condition R-第十三条> When the symbol number i is N or more and M or less (N is an integer, M is an integer, and N < M (M is smaller than N)), assume that the modulation method of s1(t) (s1(i)) (that is, the baseband signal 505A) is fixed (does not change), and the modulation method of s2(t) (s2(i)) (that is, the baseband signal 505B) is fixed (does not change).

[0181] It should be noted that the text you provided contains some possible inaccuracies or unclear parts. For example, "<条件R-第十三条>" might be a misrepresentation. It's recommended to double-check the original text for accuracy. When the symbol number i is between N and M, for all i that satisfy this, in one symbol of the signal u1(t)(u1(i)) in equation (R38), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) Then, at symbol number i, in the in-phase I-quadrature Q plane, 2 of u1(t)(u1(i)) g+h The minimum Euclidean distance between the candidate signal points is defined as D1(i). (Note that D1(i) is a real number greater than or equal to 0 (D1(i) ≥ 0). When D1(i) is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0182] In addition, when the symbol number i is between N and M, for all i that satisfy this, the number of candidate signal points in one symbol of the signal u2(t)(u2(i)) in equation (R38) on the in-phase I-quadrature Q plane is 2. g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, for symbol number i, the 2nd of u2(t)(u2(i)) in the in-phase I-quadrature Q plane is g+h The minimum Euclidean distance between the candidate signal points is defined as D2(i). (Note that D2(i) is a real number greater than or equal to 0 (D2(i) ≥ 0). When D2(i) is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0183] At this time, when the symbol number i is N or more and M or less, for all i that satisfy this condition, D1(i) > D2(i) (D1(i) is greater than D2(i)) holds. At this time, since |Q1| > |Q2| holds, the reception state of the modulation signal of z1(t) (z1(i)) (that is, u1(t) (u1(i))) may be a dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-13>, it is highly likely that the receiving device can obtain high reception quality of data. Also, even if the following conditions are satisfied, it is highly likely that the receiving device can obtain high reception quality of data.

[0184] For the same reason, when |Q1| < |Q2|, it is preferable that <Condition R-13’’> holds. <Condition R-13’’> When the symbol number i is N or more and M or less (N is an integer, M is an integer, and N < M (M is smaller than N)), assume that the modulation method of s1(t) (s1(i)) (that is, the baseband signal 505A) is fixed (does not change), and the modulation method of s2(t) (s2(i)) (that is, the baseband signal 505B) is fixed (does not change).

[0185] When the symbol number i is N or more and M or less, for all i that satisfy this condition, in one symbol of the signal u1(t) (u1(i)) of Equation (R38), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, if signal points are created in the in-phase I - quadrature Q plane for all possible values of g + h-bit data, 2 g+h pieces of signal points can be created. This number is the number of candidate signal points.) And at symbol number i, in the in-phase I - quadrature Q plane, 2 of u1(t) (u1(i)) g+hLet the minimum Euclidean distance of the candidate signal points be D1(i) (where D1(i) is a real number greater than or equal to 0 (D1(i)≥0). When D1(i) is 0, among the two signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.). g+h Among the two signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0186] Also, when the symbol number i is between N and M (inclusive), for all i that satisfy this, in one symbol of the signal u2(t) (u2(i)) of equation (R38), the number of candidate signal points in the in-phase I - quadrature Q plane is two g+h (For all possible values of the g + h - bit data in one symbol, when signal points are created in the in-phase I - quadrature Q plane, two signal points can be created. This number is the number of candidate signal points.). And at symbol number i, in the in-phase I - quadrature Q plane, let the minimum Euclidean distance of the two candidate signal points of u2(t) (u2(i)) be D2(i) (where D2(i) is a real number greater than or equal to 0 (D(i)≥0). When D2(i) is 0, among the two signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.). g+h two signal points can be created. This number is the number of candidate signal points.). And at symbol number i, in the in-phase I - quadrature Q plane, two g+h Let the minimum Euclidean distance of the two candidate signal points of u2(t) (u2(i)) be D2(i) (where D2(i) is a real number greater than or equal to 0 (D(i)≥0). When D2(i) is 0, among the two signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.). g+h Among the two signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0187] At this time, when the symbol number i is between N and M (inclusive), for all i that satisfy this, D1(i)<D2(i) (D1(i) is smaller than D2(i)) holds. In Case 10, for example, as the modulation method in s1(t) (s1(i)) and the modulation method in s2(t) (s2(i)), as described above, QPSK, 16QAM, 64QAM, 256QAM will be applied. At this time, for the specific mapping method, it will be as described above in this configuration example. However, modulation methods other than QPSK, 16QAM, 64QAM, 256QAM may also be used.

[0188] (Case 11) When a fixed precoding matrix is ​​used and equation (R8) is processed: Consider the following equation as an intermediate step in the calculation of equation (R8).

[0189]

number

[0190] (In Case 11, the precoding matrix F is a fixed precoding matrix. (However, if the modulation scheme for s1(t)(s1(i)) and / or the modulation scheme for s2(t)(s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h.

[0191] In this case, if the following conditions are met, a high spatial diversity gain can be obtained. <Condition R-14> In one symbol of the signal u1(t)(u1(i)) in equation (R39), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h (This number is the number of candidate signal points.) In addition, for one symbol of the signal u2(t)(u2(i)) in equation (R39), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h(This number is the number of candidate signal points.) In addition, in equation (R8), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), the following conditions are considered.

[0192] <Condition R-15> In one symbol of the signal u1(t)(u1(i)) in equation (R39), the number of candidate signal points in the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D1 (where D1 is a real number greater than or equal to 0 (zero) (D1 ≥ 0). When D1 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0193] In addition, for one symbol of the signal u2(t) (u2(i)) in equation (R39), the number of candidate signal points on the in-phase I-quadrature Q plane is 2 g+h (In one symbol, if you create signal points on the in-phase I-quadrature Q plane for all possible values ​​of g+h bits of data, you get 2 g+h This number is the number of candidate signal points.) Then, in the in-phase I-quadrature Q plane, g+h The minimum Euclidean distance between the candidate signal points is D2 (where D2 is a real number greater than or equal to 0 (zero) (D2 ≥ 0). When D2 is 0 (zero), 2 g+h Of these signal points, there are signal points that exist at the same position on the in-phase I-quadrature Q plane.

[0194] In this case, D1>D2 (D1 is greater than D2) holds true. Incidentally, Figure 53 shows the relationship between transmitting antennas and receiving antennas. Assume that modulated signal #1 (5301A) is transmitted from transmitting antenna #1 (5302A) of the transmitting device, and modulated signal #2 (5301B) is transmitted from transmitting antenna #2 (5302B). At this time, it is assumed that z1(t) (z1(i)) (i.e., u1(t) (u1(i))) is transmitted from transmitting antenna #1 (5302A), and z2(t) (z2(i)) (i.e., u2(t) (u2(i))) is transmitted from transmitting antenna #2 (5302B).

[0195] Then, the receiving antenna #1 (5303X) and receiving antenna #2 (5303Y) of the receiving device receive the modulated signal transmitted by the transmitting device (receiving a receiving signal 530X and a receiving signal 5304Y). At this time, the propagation coefficient of the receiving antenna #1 (5303X) from the transmitting antenna #1 (5302A) is calculated as h 11 (t), and the propagation coefficient from transmitting antenna #1 (5302A) to receiving antenna #2 (5303Y) is h 21 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #1 (5303X) is h 12 (t), and the propagation coefficient from transmitting antenna #2 (5302B) to receiving antenna #2 (5303Y) is h 22 Let (t) be the time. (t is time) In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-15>, the receiving device is more likely to be able to obtain high data reception quality.

[0196] For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-15'> be satisfied. <Condition R-15'> In one symbol of the signal u1(t) (u1(i)) of formula (R39), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of the g + h-bit data, if signal points are created in the in-phase I - quadrature Q plane, 2 g+h signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, let the minimum Euclidean distance of the 2 g+h candidate signal points of u1(t) (u1(i)) be D1 (note that D1 is a real number greater than or equal to 0 (D1≥0). When D1 is 0 (zero), among the 2 g+h signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0197] Also, in one symbol of the signal u2(t) (u2(i)) of formula (R39), in the in-phase I - quadrature Q plane, the number of candidate signal points is 2 g+h pieces. (In one symbol, for all possible values of the g + h-bit data, if signal points are created in the in-phase I - quadrature Q plane, 2 g+h signal points can be created. This number is the number of candidate signal points.) And in the in-phase I - quadrature Q plane, let the minimum Euclidean distance of the 2 g+h candidate signal points of u2(t) (u2(i)) be D2 (note that D2 is a real number greater than or equal to 0 (D2≥0). When D2 is 0 (zero), among the 2 g+h signal points, there will be signal points that exist at the same position in the in-phase I - quadrature Q plane.).

[0198] At this time, D1 < D2 (D1 is smaller than D2) holds. In Case 11, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0199] (Case 12) When using any of the precoding matrices in equations (R15) to (R30) and processing equation (R8): Consider equation (R39) as an intermediate equation in the calculation of equation (R8). In Case 12, the precoding matrix F is a fixed precoding matrix, and is expressed by any of equations (R15) to (R30). (However, if the modulation scheme for s1(t) (s1(i)) and / or the modulation scheme for s2(t) (s2(i)) is switched, the precoding matrix may be switched.) The modulation multi-level number of the modulation method of s1(t)(s1(i)) (that is, baseband signal 505A) is set to 2. g (g is an integer equal to or greater than 1), and the modulation multi-level number of the modulation method of s2(t)(s2(i)) (i.e., baseband signal 505B) is set to 2 h (h is an integer greater than or equal to 1) and g≠h. In this case, if <Condition R-14> is met, a high spatial diversity gain can be obtained.

[0200] Then, in equation (R8), when |Q1|>|Q2| (the absolute value of Q1 is greater than the absolute value of Q2), consider that <Condition R-15> is satisfied, just as in Case 11. In this case, since |Q1|>|Q2| holds, the reception state of the modulated signal z1(t)(z1(i)) (i.e., u1(t)(u1(i))) may be the dominant factor in the reception quality of the received data. Therefore, by satisfying <Condition R-15>, the receiving device is more likely to be able to obtain high data reception quality. For the same reason, when |Q1|<|Q2|, it is desirable that <Condition R-15'> be satisfied.

[0201] In Case 12, for example, as described above, QPSK, 16QAM, 64QAM, and 256QAM are applied as the modulation scheme for s1(t) (s1(i)) and the modulation scheme for s2(t) (s2(i)). In this case, the specific mapping method is as described above for this configuration example. However, modulation schemes other than QPSK, 16QAM, 64QAM, and 256QAM may also be used.

[0202] As described above in this configuration example, in a transmission method in which two modulated signals after precoding are transmitted from different antennas, by increasing the minimum Euclidean distance in the in-phase I-quadrature Q plane between the signal points of the modulated signal with the higher average transmission power, the receiving device is more likely to achieve the effect of obtaining high data reception quality.

[0203] Each of the transmitting antenna and receiving antenna described in the above configuration example may be configured with multiple antennas. Also, different antennas that transmit two modulated signals after precoding may be used to simultaneously transmit one modulated signal at different times. Furthermore, the above-described precoding method can be similarly implemented when a single carrier system, an OFDM system, a multicarrier system such as an OFDM system using wavelet transform, or a spread spectrum system is applied.

[0204] Specific examples of this embodiment will be described in detail in the following embodiments, and the operation of the receiving device will also be described. (Configuration example S1) In this configuration example, a more specific example of the precoding method when the average transmission power of the two transmission signals described in configuration example R1 is different will be described.

[0205] FIG. 5 shows an example of the configuration of a part that generates a modulated signal when the transmission method can be switched in a transmitting device of a base station (broadcast station, access point, etc.). The transmitting device of a base station (broadcast station, access point, etc.) will be described with reference to FIG.

[0206] Encoding section 502 in FIG. 5 receives information 501 and control signal 512 as input, performs encoding based on the information on the coding rate and code length (block length) included in control signal 512, and outputs encoded data 503. Mapping section 504 receives encoded data 503 and control signal 512 as input. Control signal 512 specifies that two streams are to be transmitted as the transmission method. In addition, control signal 512 specifies modulation method α and modulation method β as the modulation methods for each of the two streams. Note that modulation method α is a modulation method for modulating x-bit data, and modulation method β is a modulation method for modulating y-bit data. (For example, 16QAM (16 Quadrature Amplitude Modulation) is a modulation method for modulating 4-bit data, and 64QAM (64 Quadrature Amplitude Modulation) is a modulation method for modulating 6-bit data.) Then, mapping unit 504 modulates x bits of data out of the x+y bits of data using modulation method α to generate and output baseband signal s1(t) (505A), and also modulates the remaining y bits of data using modulation method β to output baseband signal s2(t) (505B). (Note that while FIG. 5 shows one mapping unit, an alternative configuration may include separate mapping units for generating s1(t) and s2(t). In this case, coded data 503 is distributed to the mapping unit for generating s1(t) and the mapping unit for generating s2(t).) Note that s1(t) and s2(t) are expressed as complex numbers (however, they may be either complex or real numbers), and t is time. Note that when a transmission method using multicarriers such as OFDM (Orthogonal Frequency Division Multiplexing) is used, s1 and s2 can be considered as functions of frequency f, such as s1(f) and s2(f), or as functions of time t and frequency f, such as s1(t,f) and s2(t,f). In the following, the baseband signal, precoding matrix, phase change, etc. are described as functions of time t, but they may also be considered as functions of frequency f, or functions of time t and frequency f.

[0207] Therefore, although the baseband signal, precoding matrix, phase change, and the like are sometimes described as functions of symbol number i, in this case they can be considered as functions of time t, functions of frequency f, or functions of time t and frequency f. That is, the symbols and baseband signals may be generated and arranged in the time axis direction, or may be generated and arranged in the frequency axis direction. Furthermore, the symbols and baseband signals may be generated and arranged in both the time axis direction and the frequency axis direction.

[0208] Power change unit 506A (power adjustment unit 506A) receives baseband signal s1(t) (505A) and control signal 512, sets real number P1 based on control signal 512, and outputs P1×s1(t) as power-changed signal 507A. (Note that although P1 is a real number, it may also be a complex number.) Similarly, power change unit 506B (power adjustment unit 506B) receives baseband signal s2(t) (505B) and control signal 512, sets real number P2, and outputs P2×s2(t) as power-changed signal 507B. (Note that although P2 is a real number, it may also be a complex number.) Weighting combination unit 508 receives power-modified signal 507A, power-modified signal 507B, and control signal 512 as input, and sets precoding matrix F (or F(i)) based on control signal 512. Assuming that the slot number (symbol number) is i, weighting combination unit 508 performs the following calculation.

[0209]

number

[0210] Here, a(i), b(i), c(i), and d(i) can be expressed as complex numbers (or real numbers), and three or more of a(i), b(i), c(i), and d(i) must not be 0 (zero). Note that the precoding matrix may or may not be a function of i. When the precoding matrix is ​​a function of i, the precoding matrix switches depending on the slot number (symbol number).

[0211] Then, weighting and combining section 508 outputs u1(i) in equation (S1) as weighted and combined signal 509A, and outputs u2(i) in equation (S1) as weighted and combined signal 509B. Power modification section 510A receives weighted and combined signal 509A (u1(i)) and control signal 512 as input, sets real number Q1 based on control signal 512, and outputs Q1×u1(t) as power-modified signal 511A (z1(i)). (Note that although Q1 is a real number, it may also be a complex number.) Similarly, power modification section 510B receives weighted and combined signal 509B (u2(i)) and control signal 512 as input, sets real number Q2 based on control signal 512, and outputs Q2×u2(t) as power-modified signal 511A (z2(i)). (Note that although Q2 is a real number, it may also be a complex number.) Therefore, the following equation holds:

[0212]

number

[0213] Next, a transmission method for transmitting two streams different from those in Fig. 5 will be described with reference to Fig. 6. In Fig. 6, components that operate in the same manner as in Fig. 5 are given the same reference numerals. The phase change unit 601 receives the signal 509B after weighting and combining u2(i) in the equation (S1) and the control signal 512 as input, and changes the phase of the signal 509B after weighting and combining u2(i) in the equation (S1) based on the control signal 512. Therefore, the signal after changing the phase of the signal 509B after weighting and combining u2(i) in the equation (S1) is e jθ(i) ×u2(i), and e jθ(i) The phase change unit 601 outputs ×u2(i) as the phase-changed signal 602 (j is the imaginary unit). Note that the value of the phase to be changed is a function of i, such as θ(i).

[0214] 6 each change the power of the input signal. Therefore, the outputs z1(i) and z2(i) of the power modifying units 510A and 510B in FIG. 6 are expressed by the following equations:

[0215]

number

[0216] As a method of realizing equation (S3), there is a configuration shown in Figure 7 that differs from that shown in Figure 6. The difference between Figure 6 and Figure 7 is that the order of the power change section and the phase change section is swapped. (The functions of changing the power and phase remain the same.) In this case, z1(i) and z2(i) are expressed as follows:

[0217]

number

[0218] Note that z1(i) in equation (S3) is equal to z1(i) in equation (S4), and z2(i) in equation (S3) is equal to z2(i) in equation (S4). If the phase value θ(i) to be changed in equations (S3) and (S4) is set so that θ(i+1)−θ(i) is a fixed value, the receiving device is likely to obtain good data reception quality in a radio wave propagation environment dominated by direct waves. However, the method for setting the phase value θ(i) to be changed is not limited to this example.

[0219] FIG. 8 shows an example of the configuration of a signal processing unit that processes the signals z1(i) and z2(i) obtained from FIGS. Insertion unit 804A receives signal z1(i) (801A), pilot symbol 802A, control information symbol 803A, and control signal 512 as input, inserts pilot symbol 802A and control information symbol 803A into signal (symbol) z1(i) (801A) in accordance with the frame configuration included in control signal 512, and outputs modulated signal 805A in accordance with the frame configuration.

[0220] The pilot symbols 802A and the control information symbols 803A are symbols modulated by BPSK (Binary Phase Shift Keying) or QPSK (Quadrature Phase Shift Keying) or the like (other modulation methods may also be used). Radio unit 806A receives modulated signal 805A and control signal 512 as input, and performs processing such as frequency conversion and amplification on modulated signal 805A based on control signal 512 (when OFDM is used, processing such as inverse Fourier transform is performed), and outputs transmission signal 807A, which is output as radio waves from antenna 808A.

[0221] Insertion unit 804B receives signal z2(i) (801B), pilot symbol 802B, control information symbol 803B, and control signal 512 as input, inserts pilot symbol 802B and control information symbol 803B into signal (symbol) z2(i) (801B) in accordance with the frame configuration included in control signal 512, and outputs modulated signal 805B in accordance with the frame configuration.

[0222] The pilot symbols 802B and the control information symbols 803B are symbols modulated by BPSK (Binary Phase Shift Keying) or QPSK (Quadrature Phase Shift Keying) or the like (other modulation methods may also be used). Radio unit 806B receives modulated signal 805B and control signal 512 as input, and performs processing such as frequency conversion and amplification on modulated signal 805B based on control signal 512 (when OFDM is used, processing such as inverse Fourier transform is performed), and outputs transmission signal 807B, which is output as radio waves from antenna 808B.

[0223] Here, signals z1(i) (801A) and z2(i) (801B) with the same i number are transmitted from different antennas at the same time using the same (common) frequency. (In other words, this is a transmission method using the MIMO system.) Furthermore, pilot symbol 802A and pilot symbol 802B are symbols used in the receiving device for signal detection, frequency offset estimation, gain control, channel estimation, etc., and although they are called pilot symbols here, they may also be called reference symbols or other names.

[0224] Control information symbol 803A and control information symbol 803B are symbols for transmitting to the receiving device information on the modulation method used by the transmitting device, information on the transmission method, information on the precoding method, information on the error correction code method, information on the coding rate of the error correction code, information on the block length (code length) of the error correction code, etc. Note that the control information symbol may be transmitted using only one of control information symbol 803A and control information symbol 803B.

[0225] Figure 9 shows an example of a time-frequency frame structure when transmitting two streams. In Figure 9, the horizontal axis represents frequency and the vertical axis represents time. As an example, the symbol structure for carrier 1 to carrier 38 and time $1 to time $11 is shown. FIG. 9 shows the frame structure of the transmission signal transmitted from antenna 806A in FIG. 8 and the frame of the transmission signal transmitted from antenna 808B at the same time.

[0226] In Fig. 9, in the case of a frame of a transmission signal transmitted from antenna 806A in Fig. 8, a data symbol corresponds to signal (symbol) z1(i), and a pilot symbol corresponds to pilot symbol 802A. In Fig. 9, in the case of a frame of a transmission signal transmitted from antenna 806B in Fig. 8, the data symbol corresponds to signal (symbol) z2(i), and the pilot symbol corresponds to pilot symbol 802B.

[0227] (Therefore, as explained above, in signal z1(i) (801A) and signal z2(i) (801B), signals z1(i) (801A) and z2(i) (801B) with the same i number are transmitted from different antennas at the same time using the same (common) frequency. Also, the configuration of the pilot symbols is not limited to that shown in FIG. 9, and for example, the time interval and frequency interval of the pilot symbols are not limited to that shown in FIG. 9. In addition, in FIG. 9, signals are transmitted from antenna 806A in FIG. 8 and antenna 806B in FIG. 8 at the same time using the same frequency (same (sub)carrier). Although the frame configuration is such that pilot symbols are transmitted, the present invention is not limited to this. For example, a pilot symbol may be placed on antenna 806A in FIG. 8 at time A, frequency a ((sub)carrier a), and no symbol may be placed on antenna 806B in FIG. 8 at time A, frequency a ((sub)carrier a), and no symbol may be placed on antenna 806A in FIG. 8 at time B, frequency b ((sub)carrier b), and pilot symbols may be placed on antenna 806B in FIG. 8 at time B, frequency b ((sub)carrier b).

[0228] Although only data symbols and pilot symbols are shown in FIG. 9, other symbols, such as control information symbols, may also be included in the frame. Although the examples shown in FIGS. 5 to 7 have been described with some (or all) of the power modifying units present, it is also possible that some of the power modifying units are absent. For example, in FIG. 5, if power change section 506A (power adjustment section 506A) and power change section 506B (power adjustment section 506B) do not exist, z1(i) and z2(i) are expressed as follows:

[0229]

number

[0230] Furthermore, in FIG. 5, if power change section 510A (power adjustment section 510A) and power change section 510B (power adjustment section 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0231]

number

[0232] Furthermore, in FIG. 5, if power changing unit 506A (power adjustment unit 506A), power changing unit 506B (power adjustment unit 506B), power changing unit 510A (power adjustment unit 510A), and power changing unit 510B (power adjustment unit 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0233]

number

[0234] Furthermore, in FIG. 6 or FIG. 7, if power change section 506A (power adjustment section 506A) and power change section 506B (power adjustment section 506B) are not present, z1(i) and z2(i) are expressed as follows:

[0235]

number

[0236] Furthermore, in FIG. 6 or FIG. 7, if power change section 510A (power adjustment section 510A) and power change section 510B (power adjustment section 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0237]

number

[0238] 6 or 7, if the power changing unit 506A (power adjustment unit 506A), the power changing unit 506B (power adjustment unit 506B), the power changing unit 510A (power adjustment unit 510A), and the power changing unit 510B (power adjustment unit 510B) do not exist, z1(i) and z2(i) are expressed as follows:

[0239]

number

[0240] Next, we will explain a more specific example of a precoding method when the average transmission power of the two transmission signals described in configuration example R1 is different when using the transmission method of transmitting two streams (MIMO (Multiple Input Multiple Output) method) described above. (Example 1) In the following, in mapping section 504 of Figures 5 to 7, the modulation scheme for obtaining s1(t)(s1(i)) is 16QAM, and the modulation scheme for obtaining s2(t)(s2(i)) is 64QAM, and examples of the configuration of the precoding matrix (F) and conditions for power change when precoding and / or power change are performed according to any of equations (S2), (S3), (S4), (S5), and (S8) will be described.

[0241] First, the mapping method for 16QAM will be explained. Figure 10 shows an example of a 16QAM signal point arrangement on an in-phase (I)-quadrature (Q) plane. In Figure 10, 16 circles represent 16QAM signal points, with I on the horizontal axis and Q on the vertical axis. The coordinates of the 16 signal points of 16QAM (the "circles" in Figure 10 are signal points) on the in-phase I-quadrature Q plane are (3w 16 ,3w 16), (3w 16 ,w 16 ), (3w 16 ,-w 16 ), (3w 16 ,-3w 16 ), (w 16 ,3w 16 ), (w 16 ,w 16 ), (w 16 ,-w 16 ), (w 16 ,-3w 16 ), (―w 16 ,3w 16 ), (―w 16 ,w 16 ), (―w 16 ,-w 16 ), (―w 16 ,-3w 16 ), (―3w 16 ,3w 16 ), (―3w 16 ,w 16 ), (―3w 16 ,-w 16 ), (―3w 16 ,-3w 16 ), and (w 16 is a real number greater than 0.

[0242] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, and b3. For example, if the bits to be transmitted are (b0, b1, b2, b3) = (0, 0, 0, 0), they are mapped to signal point 1001 in FIG. 10. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (3w 16 ,3w 16 ) That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 16QAM) are determined based on the bits (b0, b1, b2, b3) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3 (0000 to 1111) and the coordinates of the signal points is shown in Figure 10. The 16 signal points ("○" in Figure 10) of 16QAM (3w 16 ,3w 16 ), (3w 16 ,w 16 ), (3w 16,-w 16 ), (3w 16 ,-3w 16 ), (w 16 ,3w 16 ), (w 16 ,w 16 ), (w 16 ,-w 16 ), (w 16 ,-3w 16 ), (―w 16 ,3w 16 ), (―w 16 ,w 16 ), (―w 16 ,-w 16 ), (―w 16 ,-3w 16 ), (―3w 16 ,3w 16 ), (―3w 16 ,w 16 ), (―3w 16 ,-w 16 ), (―3w 16 ,-3w 16 ), the values ​​of the set 0000 to 1111 of b0, b1, b2, and b3 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal point ("○") immediately above the set 0000 to 1111 of b0, b1, b2, and b3 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, and b3 (0000 to 1111) and the signal point coordinates in the case of 16QAM is not limited to that shown in FIG. 10. The complex representation values ​​of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 16QAM) become the baseband signal (s1(t) or s2(t)) in FIGS. 5 to 7. The mapping method for 64QAM will now be described. Figure 11 shows an example of a 64QAM signal point arrangement on an in-phase (I)-quadrature (Q) plane. In Figure 11, 64 circles represent 64QAM signal points, with I on the horizontal axis and Q on the vertical axis.

[0243] The coordinates of the 64 signal points of 64QAM (the "circles" in FIG. 11 are signal points) on the in-phase I-quadrature Q plane are as follows: (7w 64 ,7w 64 ), (7w64 ,5w 64 )、(7w 64 ,3w 64 )、(7w 64 ,w 64 )、(7w 64 ,-w 64 )、(7w 64 ,-3w 64 )、(7w 64 ,―5w 64 )、(7w 64 ,―7w 64 ) (5w 64 ,7w 64 )、(5w 64 ,5w 64 )、(5w 64 ,3w 64 )、(5w 64 ,w 64 )、(5w 64 ,-w 64 )、(5w 64 ,-3w 64 )、(5w 64 ,―5w 64 )、(5w 64 ,―7w 64 ) (3w 64 ,7w 64 )、(3w 64 ,5w 64 )、(3w 64 ,3w 64 )、(3w 64 ,w 64 )、(3w 64 ,-w 64 )、(3w 64 ,-3w 64 )、(3w 64 ,―5w 64 )、(3w 64 ,―7w 64 ) (w 64 ,7w 64 )、(w 64 ,5w 64 )、(w 64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w 64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w 64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w 64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64,7w 64 ), (-7w 64 ,5w 64 ), (-7w 64 ,3w 64 ), (-7w 64 ,w 64 ), (-7w 64 ,-w 64 ), (-7w 64 ,-3w 64 ), (-7w 64 ,―5w 64 ), (-7w 64 ,―7w 64 ) (w 64 is a real number greater than 0.

[0244] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, and b5. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), they are mapped to signal point 1101 in FIG. 11. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (7w 64 ,7w 64 )

[0245] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the bits (b0, b1, b2, b3, b4, b5) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3, b4, b5 (000000 to 111111) and the coordinates of the signal points is shown in Figure 11. The 64 signal points ("○" in Figure 11) of 64QAM (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64 ,-w 64 ), (7w 64 ,-3w 64 ), (7w 64 ,―5w 64 ), (7w 64 ,―7w64 ) (5w 64 ,7w 64 )、(5w 64 ,5w 64 )、(5w 64 ,3w 64 )、(5w 64 ,w 64 )、(5w 64 ,-w 64 )、(5w 64 ,-3w 64 )、(5w 64 ,―5w 64 )、(5w 64 ,―7w 64 ) (3w 64 ,7w 64 )、(3w 64 ,5w 64 )、(3w 64 ,3w 64 )、(3w 64 ,w 64 )、(3w 64 ,-w 64 )、(3w 64 ,-3w 64 )、(3w 64 ,―5w 64 )、(3w 64 ,―7w 64 ) (w 64 ,7w 64 )、(w 64 ,5w 64 )、(w 64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64 ,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w 64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w 64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64 )、(-7w 64 ,w 64 )、(-7w 64 ,-w 64 )、(-7w 64 ,-3w 64 )、(-7w 64 ,―5w64 ), (-7w 64 ,―7w 64 ), the values ​​of the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") immediately above the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in the case of 64QAM is not limited to that shown in FIG. 11. The complex representation values ​​of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signal (s1(t) or s2(t)) in FIGS. 5 to 7.

[0246] In this example, in Figures 5 to 7, the modulation method of baseband signal 505A (s1(t)(s1(i))) is 16QAM, and the modulation method of baseband signal 505B (s2(t)(s2(i))) is 64QAM, and the configuration of the precoding matrix will be described. In this case, it is common to make the average power of baseband signal 505A (s1(t)(s1(i))) output by mapping unit 504 in FIGS. 5 to 7 equal to the average power of baseband signal 505B (s2(t)(s2(i))). Therefore, the coefficient w 16 And the coefficient w described in the 64QAM mapping method described above 64 The following relation holds true:

[0247]

number

[0248]

number

[0249] In the formulas (S11) and (S12), z is a real number greater than 0. <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) The precoding matrix F

[0250]

number

[0251] The configuration of and the relationship between Q1 and Q2 will be explained in detail below ((Example 1-1) to (Example 1-8)). (Example 1-1) The above <1> from <5> In either case, the precoding matrix F is set to one of the following:

[0252]

number

[0253] or

[0254]

number

[0255] or

[0256]

number

[0257] or

[0258]

number

[0259] In equations (S14), (S15), (S16), and (S17), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). In this configuration example (which is common throughout this specification), the unit of phase, such as the argument, on the complex plane is "radian." (Exceptionally, when "degree" is used, this unit is indicated.) Using the complex plane, complex numbers can be expressed in polar form as polar coordinates. When a point (a, b) on the complex plane corresponds to the complex number z = a + jb (both a and b are real numbers, and j is the imaginary unit), if this point is expressed as [r, θ] in polar coordinates, then a = r × cosθ, b=r×sinθ Formula (49) holds, r is the absolute value of z (r = |z|), and θ is the argument. And z = a + jb is re jθ Therefore, for example, in equations (S14) to (S17), e jπ However, the unit of argument π is "radian."

[0260] At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0261] When α is real:

[0262]

number

[0263] or

[0264]

number

[0265] When α is imaginary:

[0266]

number

[0267] or

[0268]

number

[0269] The modulation method for baseband signal 505A (s1(t)(s1(i))) is 16QAM, and the modulation method for baseband signal 505B (s2(t)(s2(i))) is 64QAM. Therefore, when precoding (and phase and power changes) are performed as described above and modulated signals are transmitted from each antenna, the total number of bits transmitted by the symbols transmitted from antenna 808A and antenna 808B in FIG. 8 is 10 bits, which is the sum of 4 bits (using 16QAM) and 6 bits (using 64QAM), depending on the (unit) time of time u and frequency (carrier) v.

[0270] The input bits for 16QAM mapping are b 0,16 , b 1,16 , b 2,16 , b 3,16 , the input bits for 64QAM mapping are b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 When this is the case, no matter which α is set to in equation (S18), equation (S19), equation (S20), or equation (S21), In the signal z1(t)(z1(i)), (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) exists in the in-phase I-quadrature Q plane, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) Similarly, for the signal z2(t)(z2(i)), (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b4,64 , b 5,64 ) exists on the in-phase I-quadrature Q plane from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1)

[0271] In the above, Equations (S18) to (S21) have been described as "the value of α for the receiving device to obtain good data reception quality, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8)," and this point will be explained below. In the signal z1(t)(z1(i)), (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) corresponds to (0,0,0,0,0,0,0,0,0,0,0) and the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) exists on the in-phase I-quadrature Q plane. 10 It is desired that the 1024 signal points (=1024) exist as 1024 non-overlapping signal points in the in-phase (I)-quadrature (Q) plane.

[0272] This is because, if the modulated signal transmitted from the antenna transmitting signal z2(t)(z2(i)) does not reach the receiving device, the receiving device will perform detection and error correction decoding using signal z1(t)(z1(i)). At this time, in order for the receiving device to obtain high data reception quality, it is desirable for there to be "1024 signal points without overlapping." When the precoding matrix F is set to one of the equations (S14), (S15), (S16), and (S17), and α is set as in the equations (S18), (S19), (S20), and (S21), in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,16 , b 1,16 , b2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) is arranged as shown in Figure 12, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) In Figure 12, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0273] As can be seen from Figure 12, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0274] When the precoding matrix F is set to any one of the equations (S14), (S15), (S16), and (S17), and α is set as in the equations (S18), (S19), (S20), and (S21), in the signal u2(t) (u2(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) is arranged as shown in Figure 13, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) In Figure 13, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0275] As can be seen from Fig. 13, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 12, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 13. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0276] (Example 1-2) Next, the coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0277]

number

[0278] or

[0279]

number

[0280] or

[0281]

number

[0282] or

[0283]

number

[0284] In the formulas (S22) and (S24), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0285]

number

[0286] or

[0287]

number

[0288] or

[0289]

number

[0290] or

[0291]

number

[0292] In addition, in the formulas (S26), (S27), (S28), and (S29), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0293]

number

[0294] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S22), (S23), (S24), and (S25), and θ is set to the equations (S26), (S27), (S28), and (S29), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 12. In Figure 12, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0295] As can be seen from Figure 12, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0296] Then, when the precoding matrix F is set to one of the equations (S22), (S23), (S24), and (S25), and θ is set to the equations (S26), (S27), (S28), and (S29), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 13. In Figure 13, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0297] As can be seen from Fig. 13, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 12, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 13. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0298] (Example 1-3) The coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0299]

number

[0300] or

[0301]

number

[0302] or

[0303]

number

[0304] or

[0305]

number

[0306] In equations (S31), (S32), (S33), and (S34), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0307] When α is real:

[0308]

number

[0309] or

[0310]

number

[0311] When α is imaginary:

[0312]

number

[0313] or

[0314]

number

[0315] When the precoding matrix F is set to one of the equations (S31), (S32), (S33), and (S34), and α is set to the equations (S35), (S36), (S37), and (S38), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 14. In Figure 14, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0316] As can be seen from Figure 14, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0317] Then, when the precoding matrix F is set to one of the equations (S31), (S32), (S33), and (S34), and α is set as in the equations (S35), (S36), (S37), and (S38), then, in the same way as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 15. In Figure 15, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0318] As can be seen from Fig. 15, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 14, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 15. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0319] (Example 1-4) Next, the coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0320]

number

[0321] or

[0322]

number

[0323] or

[0324]

number

[0325] or

[0326]

number

[0327] In equations (S39) and (S41), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0328]

number

[0329] or

[0330]

number

[0331] or

[0332]

number

[0333] or

[0334]

number

[0335] In the formulas (S43), (S44), (S45), and (S46), tan-1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0336]

number

[0337] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S39), (S40), (S41), and (S42), and θ is set to the equations (S43), (S44), (S45), and (S46), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) described in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is as shown in Figure 14. In FIG. 14, the horizontal axis is I, the vertical axis is Q, and the "●" indicates a signal point.

[0338] As can be seen from Figure 14, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0339] Then, when the precoding matrix F is set to one of the equations (S39), (S40), (S41), and (S42), and θ is set to the equations (S43), (S44), (S45), and (S46), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 15. In Figure 15, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0340] As can be seen from Fig. 15, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 14, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 15. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0341] (Example 1-5) The coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P12 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0342]

number

[0343] or

[0344]

number

[0345] or

[0346]

number

[0347] or

[0348]

number

[0349] In equations (S48), (S49), (S50), and (S51), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0350] When α is real:

[0351]

number

[0352] or

[0353]

number

[0354] When α is imaginary:

[0355]

number

[0356] or

[0357]

number

[0358] When the precoding matrix F is set to one of the equations (S48), (S49), (S50), and (S51), and α is set to the equations (S52), (S53), (S54), and (S55), then, in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 16. In Figure 16, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0359] As can be seen from Figure 16, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0360] Then, when the precoding matrix F is set to one of the equations (S48), (S49), (S50), and (S51), and α is set to the equations (S52), (S53), (S54), and (S55), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 17. In Figure 17, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0361] As can be seen from Fig. 17, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let the minimum Euclidean distance of the 1024 signal points in FIG. 16 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 17 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0362] (Example 1-6) Next, regarding the coefficient w described in the above-mentioned 16QAM mapping method 16 and the coefficient w described in the above-mentioned 64QAM mapping method 64 [[ID=第十二]]Regarding these, equations (S11) and (S12) hold, <1>In equation (S2), when P1 <第0002090号>= P2 2 <2>In equation (S3), when P1 2 = P2 2 <3>In equation (S4), when P1 <000第02094号>= P2 2 <4>In the case of equation (S5) <5>In the case of equation (S8) Consider the case where the precoding matrix F when performing the operations of

[0363] [Number] <001621@2>

[0364] Or

[0365] [Number] <001622第1号>

[0366] Or

[0367] [Number] ​​

[0368] or

[0369]

number

[0370] In equations (S56) and (S58), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0371]

number

[0372] or

[0373]

number

[0374] or

[0375]

number

[0376] or

[0377]

number

[0378] In the formulas (S60), (S61), (S62), and (S63), tan -1(x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0379]

number

[0380] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S56), (S57), (S58), and (S59), and θ is set to the equations (S60), (S61), (S62), and (S63), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) described in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is as shown in Figure 16. In FIG. 16, the horizontal axis is I, the vertical axis is Q, and the "●" indicates a signal point.

[0381] As can be seen from Figure 16, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0382] And when the precoding matrix F is set to any one of Equation (S56), Equation (S57), Equation (S58), and Equation (S59), and θ is set as in Equation (S60), Equation (S61), Equation (S62), and Equation (S63), considering the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) corresponds to the signal point from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) in the configuration example R1, and the arrangement of the signal points in the in-phase I - quadrature Q plane in the signal u1(t) (u1(i)) is as shown in FIG. 17. In FIG. 17, the horizontal axis is I, the vertical axis is Q, and "●" represents the signal points.

[0383] As can be seen from FIG. 17, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility of obtaining high reception quality in the receiving device. Let the minimum Euclidean distance of the 1024 signal points in FIG. 16 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 17 be D1. Then, D1 < D2 holds. Therefore, from the configuration example R1, in Equation (S2), Equation (S3), Equation (S4), Equation (S5), and Equation (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0384] (Example 1 - 7) Regarding the coefficient w described in the above-described 16QAM mapping method and the coefficient w described in the above-described 64QAM mapping method, Equation (S11) and Equation (S12) hold, 16 and regarding the coefficient w described in the above-described 64QAM mapping method, Equation (S11) and Equation (S12) hold, 64 Equation (S11) and Equation (S12) hold, <1>In Equation (S2), when P1 2 = P2 2 is set <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0385]

number

[0386] or

[0387]

number

[0388] or

[0389]

number

[0390] or

[0391]

number

[0392] In equations (S65), (S66), (S67), and (S68), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0393] When α is real:

[0394]

number

[0395] or

[0396]

number

[0397] When α is imaginary:

[0398]

number

[0399] or

[0400]

number

[0401] When the precoding matrix F is set to one of the equations (S65), (S66), (S67), and (S68), and α is set to the equations (S69), (S70), (S71), and (S72), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 18. In Figure 18, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0402] As can be seen from Figure 18, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0403] Then, when the precoding matrix F is set to one of the equations (S65), (S66), (S67), and (S68), and α is set to the equations (S69), (S70), (S71), and (S72), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 19. In Figure 19, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0404] As can be seen from Fig. 19, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let the minimum Euclidean distance of the 1024 signal points in FIG. 18 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 19 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0405] (Example 1-8) Next, regarding the coefficient w described in the 16QAM mapping method explained above 16 and the coefficient w described in the 64QAM mapping method explained above 64 equations (S11) and (S12) hold, <1>In equation (S2), when P1 2 = P2 2 <2>In equation (S3), when P1 2 = P2 2 <3>In equation (S4), when P1 2 = P2 2 <4>In the case of equation (S5) <5>In the case of equation (S8) Consider the case where the precoding matrix F when performing the operations of

[0406]

Number

[0407] Or,

[0408]

Number

[0409] Or,

[0410]

Number

[0411] or

[0412]

number

[0413] In the formulas (S73) and (S75), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0414]

number

[0415] or

[0416]

number

[0417] or

[0418]

number

[0419] or

[0420]

number

[0421] In addition, in the formulas (S77), (S78), (S79), and (S80), tan-1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0422]

number

[0423] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S73), (S74), (S75), and (S76), and θ is set to the equations (S77), (S78), (S79), and (S80), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 18. In Figure 18, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0424] As can be seen from Figure 18, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0425] Then, when the precoding matrix F is set to any one of Expression (S73), Expression (S74), Expression (S75), and Expression (S76), and θ is set as in Expression (S77), Expression (S78), Expression (S79), and Expression (S80), considering the same as above, (b 0,16 b 1,16 b 2,16 b 3,16 b 0,64 b 1,64 b 2,64 b 3,64 b 4,64 b 5,64 ) corresponds to the signal point from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) in the configuration example R1 of the signal u1(t) (u1(i)) in the in-phase I - quadrature Q plane is as shown in FIG. 19. In FIG. 19, the horizontal axis is I, the vertical axis is Q, and "●" is the signal point.

[0426] As can be seen from FIG. 19, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility of obtaining high reception quality in the receiving device. Let the minimum Euclidean distance of the 1024 signal points in FIG. 18 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 19 be D1. Then, D1 < D2 holds. Therefore, from the configuration example R1, in Expression (S2), Expression (S3), Expression (S4), Expression (S5), and Expression (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0427] (Example 1 - Supplementary) In (Example 1 - 1) to (Example 1 - 8), examples of the value of α and examples of the value of θ that may obtain high data reception quality were shown. However, even if the values of α and θ are not these values, high data reception quality may be obtained by satisfying the conditions shown in the configuration example R1.

[0428] (Example 2) In the following, in mapping section 504 of Figures 5 to 7, the modulation scheme for obtaining s1(t)(s1(i)) is 64QAM, and the modulation scheme for obtaining s2(t)(s2(i)) is 16QAM, and examples of the configuration of the preceding matrix (F) and conditions for power change when preceding and / or power change is performed according to any of equations (S2), (S3), (S4), (S5), and (S8) will be described.

[0429] First, the mapping method for 16QAM will be explained. Figure 10 shows an example of a 16QAM signal point arrangement on an in-phase (I)-quadrature (Q) plane. In Figure 10, 16 circles represent 16QAM signal points, with I on the horizontal axis and Q on the vertical axis. The coordinates of the 16 signal points of 16QAM (the "circles" in Figure 10 are signal points) on the in-phase I-quadrature Q plane are (3w 16 ,3w 16 ), (3w 16 ,w 16 ), (3w 16 ,-w 16 ), (3w 16 ,-3w 16 ), (w 16 ,3w 16 ), (w 16 ,w 16 ), (w 16 ,-w 16 ), (w 16 ,-3w 16 ), (―w 16 ,3w 16 ), (―w 16 ,w 16 ), (―w 16 ,-w 16 ), (―w 16 ,-3w 16 ), (―3w 16 ,3w 16 ), (―3w 16 ,w 16 ), (―3w 16 ,-w 16 ), (―3w 16 ,-3w 16 ), and (w 16 is a real number greater than 0.

[0430] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, and b3. For example, if the bits to be transmitted are (b0, b1, b2, b3) = (0, 0, 0, 0), they are mapped to signal point 1001 in FIG. 10. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (3w 16 ,3w 16 ) That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 16QAM) are determined based on the bits (b0, b1, b2, b3) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3 (0000 to 1111) and the coordinates of the signal points is shown in Figure 10. The 16 signal points ("○" in Figure 10) of 16QAM (3w 16 ,3w 16 ), (3w 16 ,w 16 ), (3w 16 ,-w 16 ), (3w 16 ,-3w 16 ), (w 16 ,3w 16 ), (w 16 ,w 16 ), (w 16 ,-w 16 ), (w 16 ,-3w 16 ), (―w 16 ,3w 16 ), (―w 16 ,w 16 ), (―w 16 ,-w 16 ), (―w 16 ,-3w 16 ), (―3w 16 ,3w 16 ), (―3w 16 ,w 16 ), (―3w 16 ,-w 16 ), (―3w 16 ,-3w 16), the values ​​of the set 0000 to 1111 of b0, b1, b2, and b3 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal point ("○") immediately above the set 0000 to 1111 of b0, b1, b2, and b3 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, and b3 (0000 to 1111) and the signal point coordinates in the case of 16QAM is not limited to that shown in FIG. 10. The complex representation values ​​of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 16QAM) become the baseband signal (s1(t) or s2(t)) in FIGS. 5 to 7.

[0431] The mapping method for 64QAM will now be described. Figure 11 shows an example of a 64QAM signal point arrangement on an in-phase (I)-quadrature (Q) plane. In Figure 11, 64 circles represent 64QAM signal points, with I on the horizontal axis and Q on the vertical axis. The coordinates of the 64 signal points of 64QAM (the "circles" in FIG. 11 are signal points) on the in-phase I-quadrature Q plane are as follows: (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64 ,-w 64 ), (7w 64 ,-3w 64 ), (7w 64 ,―5w 64 ), (7w 64 ,―7w 64 ) (5w 64 ,7w 64 ), (5w 64 ,5w 64 ), (5w 64 ,3w 64 ), (5w 64 ,w 64 ), (5w 64 ,-w 64 ), (5w 64 ,-3w 64 ), (5w 64,―5w 64 )、(5in 64 ,―7w 64 ) (3in 64 ,7w 64 )、(3in 64 ,5w 64 )、(3in 64 ,3in 64 )、(3in 64 ,In 64 )、(3in 64 ,-In 64 )、(3in 64 ,-3w 64 )、(3in 64 ,―5w 64 )、(3in 64 ,―7w 64 ) (In 64 ,7w 64 ),(In 64 ,5w 64 ),(In 64 ,3in 64 ),(In 64 ,In 64 ),(In 64 ,-In 64 ),(In 64 ,-3w 64 ),(In 64 ,―5w 64 ),(In 64 ,―7w 64 ) (-In 64 ,7w 64 ),(-In 64 ,5w 64 ),(-In 64 ,3in 64 ),(-In 64 ,In 64 ),(-In 64 ,-In 64 ),(-In 64 ,-3w 64 ),(-In 64 ,―5w 64 ),(-In 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64), (-3w 64 ,3w 64 ), (-3w 64 ,w 64 ), (-3w 64 ,-w 64 ), (-3w 64 ,-3w 64 ), (-3w 64 ,―5w 64 ), (-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 ), (-5w 64 ,5w 64 ), (-5w 64 ,3w 64 ), (-5w 64 ,w 64 ), (-5w 64 ,-w 64 ), (-5w 64 ,-3w 64 ), (-5w 64 ,―5w 64 ), (-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 ), (-7w 64 ,5w 64 ), (-7w 64 ,3w 64 ), (-7w 64 ,w 64 ), (-7w 64 ,-w 64 ), (-7w 64 ,-3w 64 ), (-7w 64 ,―5w 64 ), (-7w 64 ,―7w 64 ) (w 64 is a real number greater than 0.

[0432] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, and b5. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), they are mapped to signal point 1101 in FIG. 11. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (7w 64 ,7w 64 )

[0433] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the bits (b0, b1, b2, b3, b4, b5) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3, b4, b5 (000000 to 111111) and the coordinates of the signal points is shown in Figure 11. The 64 signal points ("○" in Figure 11) of 64QAM (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64 ,-w 64 ), (7w 64 ,-3w 64 ), (7w 64 ,―5w 64 ), (7w 64 ,―7w 64 ) (5w 64 ,7w 64 ), (5w 64 ,5w 64 ), (5w 64 ,3w 64 ), (5w 64 ,w 64 ), (5w 64 ,-w 64 ), (5w 64 ,-3w 64 ), (5w 64 ,―5w 64 ), (5w 64 ,―7w 64 ) (3w 64 ,7w 64 ), (3w64 ,5w 64 )、(3in 64 ,3in 64 )、(3in 64 ,In 64 )、(3in 64 ,-In 64 )、(3in 64 ,-3w 64 )、(3in 64 ,―5w 64 )、(3in 64 ,―7w 64 ) (In 64 ,7w 64 ),(In 64 ,5w 64 ),(In 64 ,3in 64 ),(In 64 ,In 64 ),(In 64 ,-In 64 ),(In 64 ,-3w 64 ),(In 64 ,―5w 64 ),(In 64 ,―7w 64 ) (-In 64 ,7w 64 ),(-In 64 ,5w 64 ),(-In 64 ,3in 64 ),(-In 64 ,In 64 ),(-In 64 ,-In 64 ),(-In 64 ,-3w 64 ),(-In 64 ,―5w 64 ),(-In 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3in 64 )、(-3w 64 ,In 64 )、(-3w 64 ,-In 64)、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64 )、(-7w 64 ,w 64 )、(-7w 64 ,-w 64 )、(-7w 64 ,-3w 64 )、(-7w 64 ,―5w 64 )、(-7w 64 ,―7w 64), the values ​​of the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") immediately above the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in the case of 64QAM is not limited to that shown in FIG. 11. The complex representation values ​​of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signal (s1(t) or s2(t)) in FIGS. 5 to 7.

[0434] In this example, in Figures 5 to 7, the modulation method of baseband signal 505A (s1(t)(s1(i))) is 64QAM, and the modulation method of baseband signal 505B (s2(t)(s2(i))) is 16QAM, and the configuration of the precoding matrix will be described. In this case, it is common to make the average power of baseband signal 505A (s1(t)(s1(i))) output by mapping unit 504 in FIGS. 5 to 7 equal to the average power of baseband signal 505B (s2(t)(s2(i))). Therefore, the coefficient w 16 And the coefficient w described in the 64QAM mapping method described above 64 The following relation holds true:

[0435]

number

[0436]

number

[0437] In the formulas (S82) and (S83), z is a real number greater than 0. <1> In equation (S2), P12 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) The precoding matrix F

[0438]

number

[0439] The configuration of and the relationship between Q1 and Q2 will be explained in detail below ((Example 2-1) to (Example 2-8)). (Example 2-1) The above <1> from <5> In either case, the precoding matrix F is set to one of the following:

[0440]

number

[0441] or

[0442]

number

[0443] or

[0444]

number

[0445] or

[0446]

number

[0447] In equations (S85), (S86), (S87), and (S88), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0448] When α is real:

[0449]

number

[0450] or

[0451]

number

[0452] When α is imaginary:

[0453]

number

[0454] or

[0455]

number

[0456] The modulation method for baseband signal 505A (s1(t)(s1(i))) is 64QAM, and the modulation method for baseband signal 505B (s2(t)(s2(i))) is 16QAM. Therefore, when precoding (and phase and power changes) are performed as described above and modulated signals are transmitted from each antenna, the total number of bits transmitted by the symbols transmitted from antenna 808A and antenna 808B in FIG. 8 is 10 bits, which is the sum of 4 bits (using 16QAM) and 6 bits (using 64QAM), depending on the (unit) time of time u and frequency (carrier) v.

[0457] The input bits for 16QAM mapping are b 0,16 , b 1,16 , b 2,16 , b 3,16 , the input bits for 64QAM mapping are b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 When this is the case, no matter which α is set to in equation (S89), equation (S90), equation (S91), or equation (S92), In the signal z1(t)(z1(i)), (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) exists in the in-phase I-quadrature Q plane, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) Similarly, for the signal z2(t)(z2(i)), (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b3,64 , b 4,64 , b 5,64 ) exists on the in-phase I-quadrature Q plane from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1)

[0458] In the above, Equations (S89) to (S92) have been described as "the value of α for the receiving device to obtain good data reception quality, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8)," and this point will now be explained. In the signal z2(t)(z2(i)), (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) corresponds to (0,0,0,0,0,0,0,0,0,0,0) and the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) exists on the in-phase I-quadrature Q plane. 10 It is desired that the 1024 signal points (=1024) exist as 1024 non-overlapping signal points in the in-phase (I)-quadrature (Q) plane.

[0459] This is because, if the modulated signal transmitted from the antenna transmitting signal z1(t)(z1(i)) does not reach the receiving device, the receiving device will perform detection and error correction decoding using signal z2(t)(z2(i)). At this time, in order for the receiving device to obtain high data reception quality, it is desirable for there to be "1024 signal points without overlapping." When the precoding matrix F is set to any one of the equations (S85), (S86), (S87), and (S88), and α is set as in the equations (S89), (S90), (S91), and (S92), in the signal u2(t) (u2(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,16 , b1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) is arranged as shown in Figure 16, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) In Figure 16, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0460] As can be seen from Figure 16, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0461] Then, when the precoding matrix F is set to any one of the formulas (S85), (S86), (S87), and (S88), and α is set as in the formulas (S89), (S90), (S91), and (S92), in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) is arranged as shown in Figure 17, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1) In Figure 17, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0462] As can be seen from Fig. 17, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Then, let the minimum Euclidean distance of the 1024 signal points in FIG. 16 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 17 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0463] (Example 2-2) Next, regarding the coefficient w described in the 16QAM mapping method explained above 16 and the coefficient w described in the 64QAM mapping method explained above 64 equations (S11) and (S1) hold, <1> In equation (S2), when P1 2 = P2 2 <2> In equation (S3), when P1 2 = P2 2 <3> In equation (S4), when P1 2 = P2 2 <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the operations of

[0464]

Number

[0465] Or,

[0466]

Number

number

[0469] or

[0470]

number

[0471] In the formulas (S93) and (S95), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0472]

number

[0473] or

[0474]

number

[0475] or

[0476]

number

[0477] or

[0478]

number

[0479] In addition, in the formulas (S97), (S98), (S99), and (S100), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0480]

number

[0481] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S93), (S94), (S95), and (S96), and θ is set to the equations (S97), (S98), (S99), and (S100), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 16. In Figure 16, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0482] As can be seen from Figure 16, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0483] Then, when the pre-coding matrix F is set to any of Expression (S93), Expression (S94), Expression (S95), and Expression (S96), and θ is set as in Expression (S97), Expression (S98), Expression (S99), and Expression (S100), considering the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) corresponds to the signal point from the signal point corresponding to (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) in the configuration example R1 of the signal u1(t) (u1(i)) in the in-phase I - quadrature Q plane is as shown in FIG. 17. In FIG. 17, the horizontal axis is I, the vertical axis is Q, and "●" is the signal point.

[0484] As can be seen from FIG. 17, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility of obtaining high reception quality in the receiving device. Then, let the minimum Euclidean distance of the 1024 signal points in FIG. 16 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 17 be D1. Then, D1 < D2 holds. Therefore, from the configuration example R1, in Expression (S2), Expression (S3), Expression (S4), Expression (S5), and Expression (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0485] (Example 2 - 3) Regarding the coefficient w described in the above-described 16QAM mapping method and the coefficient w described in the above-described 64QAM mapping method, Expression (S11) and Expression (S12) hold, 16 and regarding the coefficient w described in the above-described 64QAM mapping method, 64 Expression (S11) and Expression (S12) hold, <1>In Expression (S2), P1 2 = P22 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0486]

number

[0487] or

[0488]

number

[0489] or

[0490]

number

[0491] or

[0492]

number

[0493] In equations (S102), (S103), (S104), and (S105), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0494] When α is real:

[0495]

number

[0496] or

[0497]

number

[0498] When α is imaginary:

[0499]

number

[0500] or

[0501]

number

[0502] When the precoding matrix F is set to one of the formulas (S102), (S103), (S104), and (S105), and α is set to one of the formulas (S106), (S107), (S108), and (S109), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 18. In Figure 18, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0503] As can be seen from Figure 18, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0504] Then, when the precoding matrix F is set to any one of the formulas (S102), (S103), (S104), and (S105), and α is set to any one of the formulas (S106), (S107), (S108), and (S109), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 19. In Figure 19, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0505] As can be seen from Fig. 19, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let the minimum Euclidean distance of the 1024 signal points in FIG. 18 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 19 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0506] (Example 2-4) Next, regarding the coefficient w described in the 16QAM mapping method explained above 16 and the coefficient w described in the 64QAM mapping method explained above 64 equations (S11) and (S12) hold, <1>In equation (S2), when P1 2 = P2 2 <2>In equation (S3), when P1 2 = P2 2 <3>In equation (S4), when P1 2 = P2 2 <4>In the case of equation (S5) <5>In the case of equation (S8) Consider the case where the precoding matrix F when performing the operations of

[0507]

Number

[0508] Or

[0509]

Number

[0510] Or

[0511]

Number

[0512] or

[0513]

number

[0514] In the formulas (S110) and (S112), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0515]

number

[0516] or

[0517]

number

[0518] or

[0519]

number

[0520] or

[0521]

number

[0522] In addition, in the formulas (S114), (S115), (S116), and (S117), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0523]

number

[0524] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S110), (S111), (S112), and (S113), and θ is set to the equations (S114), (S115), (S116), and (S117), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 18. In Figure 18, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0525] As can be seen from FIG. 18, it can be understood that there are 1024 signal points without overlapping. Among the 1024 signal points in the in-phase I - quadrature Q plane, the Euclidean distances between the 1020 signal points excluding the four signal points at the far right and top, far right and bottom, far left and top, and far left and bottom and their closest other signal points are equal to each other. Therefore, there is a high possibility of obtaining high reception quality in the receiving device.

[0526] And when the precoding matrix F is set to any of the expressions (S110), (S111), (S112), (S113) and θ is set as in the expressions (S114), (S115), (S116), (S117), considering the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 ) corresponding to the signal point from (0, 0, 0, 0, 0, 0, 0, 0, 0, 0) to the signal point corresponding to (1, 1, 1, 1, 1, 1, 1, 1, 1, 1) in the signal u1(t) (u1(i)) described in the configuration example R1, the arrangement of the signal points in the in-phase I - quadrature Q plane is as shown in FIG. 19. In FIG. 19, the horizontal axis is I, the vertical axis is Q, and "●" represents the signal points.

[0527] As can be seen from FIG. 19, it can be understood that there are 1024 signal points without overlapping. Therefore, there is a high possibility of obtaining high reception quality in the receiving device. And let the minimum Euclidean distance of the 1024 signal points in FIG. 18 be D2, and the minimum Euclidean distance of the 1024 signal points in FIG. 19 be D1. Then, D1 < D2 holds. Therefore, from the configuration example R1, in the expressions (S2), (S3), (S4), (S5), (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0528] (Example 2 - 5) The coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0529]

number

[0530] or

[0531]

number

[0532] or

[0533]

number

[0534] or

[0535]

number

[0536] In equations (S119), (S120), (S121), and (S122), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0537] When α is real:

[0538]

number

[0539] or

[0540]

number

[0541] When α is imaginary:

[0542]

number

[0543] or

[0544]

number

[0545] When the precoding matrix F is set to one of the formulas (S119), (S120), (S121), and (S122), and α is set to one of the formulas (S123), (S124), (S125), and (S126), the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 12. In Figure 12, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0546] As can be seen from Figure 12, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0547] Then, when the precoding matrix F is set to one of the formulas (S119), (S120), (S121), and (S122), and α is set to the formulas (S123), (S124), (S125), and (S126), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 13. In Figure 13, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0548] As can be seen from Fig. 13, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 12, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 13. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0549] (Example 2-6) Next, the coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0550]

number

[0551] or

[0552]

number

[0553] or

[0554]

number

[0555] or

[0556]

number

[0557] In the formulas (S127) and (S129), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0558]

number

[0559] or

[0560]

number

[0561] or

[0562]

number

[0563] or

[0564]

number

[0565] In the formulas (S131), (S132), (S133), and (S134), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0566]

number

[0567] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S127), (S128), (S129), and (S130), and θ is set to the equations (S131), (S132), (S133), and (S134), as described above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 12. In Figure 12, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0568] As can be seen from Figure 12, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0569] Then, when the precoding matrix F is set to one of the equations (S127), (S128), (S129), and (S130), and θ is set to the equations (S131), (S132), (S133), and (S134), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 13. In Figure 13, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0570] As can be seen from Fig. 13, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 12, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 13. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0571] (Example 2-7) The coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0572]

number

[0573] or

[0574]

number

[0575] or

[0576]

number

[0577] or

[0578]

number

[0579] In equations (S136), (S137), (S138), and (S139), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0580] When α is real:

[0581]

number

[0582] or

[0583]

number

[0584] When α is imaginary:

[0585]

number

[0586] or

[0587]

number

[0588] The precoding matrix F is expressed as (S136), (S137), (S138), and (S 139) and set α as in equation (S140), equation (S141), equation (S142), or equation (S143), then, in the same way as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 14. In Figure 14, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0589] As can be seen from Figure 14, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0590] Then, when the precoding matrix F is set to one of the equations (S136), (S137), (S138), and (S139), and α is set to the equations (S140), (S141), (S142), and (S143), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 15. In Figure 15, the horizontal axis is I, the vertical axis is Q, and the "●"s are signal points.

[0591] As can be seen from Fig. 15, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 14, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 15. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0592] (Example 2-8) Next, the coefficient w described in the 16QAM mapping method explained above 16 And the coefficient w described in the 64QAM mapping method described above 64 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0593]

number

[0594] or

[0595]

number

[0596] or

[0597]

number

[0598] or

[0599]

number

[0600] In equations (S144) and (S146), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0601]

number

[0602] or

[0603]

number

[0604] or

[0605]

number

[0606] or

[0607]

number

[0608] In addition, in the formulas (S148), (S149), (S150), and (S151), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0609]

number

[0610] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S144), (S145), (S146), and (S147), and θ is set to one of the equations (S148), (S149), (S150), and (S151), considering the same as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64The arrangement of signal points on the in-phase I-quadrature Q plane for signal u1(t) (u1(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 14. In Figure 14, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0611] As can be seen from Figure 14, there are 1024 non-overlapping signal points. Furthermore, of the 1024 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal, excluding the four signal points at the top right, bottom right, top left, and bottom left. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0612] Then, when the precoding matrix F is set to one of the equations (S144), (S145), (S146), and (S147), and θ is set to the equations (S148), (S149), (S150), and (S151), in the same manner as above, (b 0,16 , b 1,16 , b 2,16 , b 3,16 , b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 The arrangement of signal points on the in-phase I-quadrature Q plane for signal u2(t) (u2(i)) explained in configuration example R1, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1), is shown in Figure 15. In Figure 15, the horizontal axis is I, the vertical axis is Q, and the "●"s represent signal points.

[0613] As can be seen from Fig. 15, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance of the 1024 signal points in Fig. 14, and D2 be the minimum Euclidean distance of the 1024 signal points in Fig. 15. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0614] (Example 2 - Supplement) In (Example 2-1) to (Example 2-8), examples of values ​​of α and θ that may result in high data reception quality are shown, but even if the values ​​of α and θ are not these values, high data reception quality may be obtained by satisfying the conditions shown in configuration example R1.

[0615] (Example 3) In the following, in mapping section 504 of Figures 5 to 7, the modulation scheme for obtaining s1(t)(s1(i)) is 64QAM, and the modulation scheme for obtaining s2(t)(s2(i)) is 256QAM, and examples of the configuration of the precoding matrix (F) and conditions for power change when precoding and / or power change are performed according to any of equations (S2), (S3), (S4), (S5), and (S8) will be described. First, the mapping method for 64QAM will be explained. Figure 11 shows an example of a 64QAM signal point arrangement on an in-phase (I)-quadrature (Q) plane. In Figure 11, 64 circles represent 64QAM signal points, with I on the horizontal axis and Q on the vertical axis.

[0616] The coordinates of the 64 signal points of 64QAM (the "circles" in FIG. 11 are signal points) on the in-phase I-quadrature Q plane are as follows: (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64,-w 64 )、(7w 64 ,-3w 64 )、(7w 64 ,―5w 64 )、(7w 64 ,―7w 64 ) (5w 64 ,7w 64 )、(5w 64 ,5w 64 )、(5w 64 ,3w 64 )、(5w 64 ,w 64 )、(5w 64 ,-w 64 )、(5w 64 ,-3w 64 )、(5w 64 ,―5w 64 )、(5w 64 ,―7w 64 ) (3w 64 ,7w 64 )、(3w 64 ,5w 64 )、(3w 64 ,3w 64 )、(3w 64 ,w 64 )、(3w 64 ,-w 64 )、(3w 64 ,-3w 64 )、(3w 64 ,―5w 64 )、(3w 64 ,―7w 64 ) (w 64 ,7w 64 )、(w 64 ,5w 64 )、(w 64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64 ,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w 64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w 64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64 )、(-7w 64 ,w64 ), (-7w 64 ,-w 64 ), (-7w 64 ,-3w 64 ), (-7w 64 ,―5w 64 ), (-7w 64 ,―7w 64 ) (w 64 is a real number greater than 0.

[0617] Here, the bits to be transmitted (input bits) are b0, b1, b2, b3, b4, and b5. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), they are mapped to signal point 1101 in FIG. 11. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (7w 64 ,7w 64 )

[0618] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the bits (b0, b1, b2, b3, b4, b5) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3, b4, b5 (000000 to 111111) and the coordinates of the signal points is shown in Figure 11. The 64 signal points ("○" in Figure 11) of 64QAM (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64 ,-w 64 ), (7w 64 ,-3w 64 ), (7w 64 ,―5w 64 ), (7w 64 ,―7w 64 ) (5w 64 ,7w 64 ), (5w 64 ,5w 64 ), (5w 64,3in 64 )、(5in 64 ,In 64 )、(5in 64 ,-In 64 )、(5in 64 ,-3w 64 )、(5in 64 ,―5w 64 )、(5in 64 ,―7w 64 ) (3in 64 ,7w 64 )、(3in 64 ,5w 64 )、(3in 64 ,3in 64 )、(3in 64 ,In 64 )、(3in 64 ,-In 64 )、(3in 64 ,-3w 64 )、(3in 64 ,―5w 64 )、(3in 64 ,―7w 64 ) (In 64 ,7w 64 ),(In 64 ,5w 64 ),(In 64 ,3in 64 ),(In 64 ,In 64 ),(In 64 ,-In 64 ),(In 64 ,-3w 64 ),(In 64 ,―5w 64 ),(In 64 ,―7w 64 ) (-In 64 ,7w 64 ),(-In 64 ,5w 64 ),(-In 64 ,3in 64 ),(-In 64 ,In 64 ),(-In 64 ,-In 64 ),(-In 64 ,-3w 64 ),(-In 64,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64 )、(-7w 64 ,w 64 )、(-7w 64 ,-w 64 )、(-7w 64 ,-3w 64 )、(-7w 64 ,―5w 64 )、(-7w 64 ,―7w 64), the values ​​of the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") immediately above the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in the case of 64QAM is not limited to that shown in FIG. 11. The complex representation values ​​of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signal (s1(t) or s2(t)) in FIGS. 5 to 7. The mapping method for 256QAM will now be described. Figure 20 shows an example of a 256QAM signal point arrangement on the in-phase I-quadrature Q plane. In Figure 20, the 256 circles represent 256QAM signal points.

[0619] The coordinates of the 256 signal points of 256QAM (the "circles" in FIG. 20 are signal points) on the in-phase I-quadrature Q plane are as follows: (15w 256 ,15w 256 ), (15w 256 ,13w 256 ), (15w 256 ,11w 256 ), (15w 256 ,9w 256 ), (15w 256 ,7w 256 ), (15w 256 ,5w 256 ), (15w 256 ,3w 256 ), (15w 256 ,w 256 ), (15w 256 ,―15w 256 ), (15w 256 ,―13w 256 ), (15w 256 ,―11w 256 ), (15w 256 ,―9w 256 ), (15w 256 ,―7w256 )、(15w 256 ,―5w 256 )、(15w 256 ,―3w 256 )、(15w 256 ,-In 256 )、 (13in 256 ,15in 256 )、(13w 256 ,13w 256 )、(13w 256 ,11in 256 )、(13w 256 ,9w 256 )、(13w 256 ,7w 256 )、(13w 256 ,5w 256 )、(13w 256 ,3in 256 )、(13w 256 ,In 256 )、 (13in 256 ,―15w 256 )、(13w 256 ,―13w 256 )、(13w 256 ,―11w 256 )、(13w 256 ,―9w 256 )、(13w 256 ,―7w 256 )、(13w 256 ,―5w 256 )、(13w 256 ,―3w 256 )、(13w 256 ,-In 256 )、 (11in 256 ,15in 256 )、(11w 256 ,13w 256 )、(11w 256 ,11in 256 )、(11w 256 ,9w 256 )、(11w 256 ,7w 256 )、(11w 256 ,5w 256 )、(11w 256 ,3in 256)、(11w 256 ,In 256 )、 (11in 256 ,―15w 256 )、(11w 256 ,―13w 256 )、(11w 256 ,―11w 256 )、(11w 256 ,―9w 256 )、(11w 256 ,―7w 256 )、(11w 256 ,―5w 256 )、(11w 256 ,―3w 256 )、(11w 256 ,-In 256 )、 (9in 256 ,15in 256 )、(9w 256 ,13w 256 )、(9w 256 ,11in 256 )、(9w 256 ,9w 256 )、(9w 256 ,7w 256 )、(9w 256 ,5w 256 )、(9w 256 ,3in 256 )、(9w 256 ,In 256 )、 (9in 256 ,―15w 256 )、(9w 256 ,―13w 256 )、(9w 256 ,―11w 256 )、(9w 256 ,―9w 256 )、(9w 256 ,―7w 256 )、(9w 256 ,―5w 256 )、(9w 256 ,―3w 256 )、(9w 256 ,-In 256 )、 (7in 256 ,15in 256 )、(7w256 ,13w 256 )、(7w 256 ,11in 256 )、(7w 256 ,9w 256 )、(7w 256 ,7w 256 )、(7w 256 ,5w 256 )、(7w 256 ,3in 256 )、(7w 256 ,In 256 )、 (7in 256 ,―15w 256 )、(7w 256 ,―13w 256 )、(7w 256 ,―11w 256 )、(7w 256 ,―9w 256 )、(7w 256 ,―7w 256 )、(7w 256 ,―5w 256 )、(7w 256 ,―3w 256 )、(7w 256 ,-In 256 )、 (5in 256 ,15in 256 )、(5in 256 ,13w 256 )、(5in 256 ,11in 256 )、(5in 256 ,9w 256 )、(5in 256 ,7w 256 )、(5in 256 ,5w 256 )、(5in 256 ,3in 256 )、(5in 256 ,In 256 )、 (5in 256 ,―15w 256 )、(5in 256 ,―13w 256 )、(5in 256 ,―11w 256 )、(5in 256 ,―9w 256 )、(5in 256,―7w 256 )、(5w 256 ,―5w 256 )、(5w 256 ,―3w 256 )、(5w 256 ,―w 256 )、 (3w 256 15w 256 )、(3w 256 ,13w 256 )、(3w 256 ,11w 256 )、(3w 256 ,9w 256 )、(3w 256 ,7w 256 )、(3w 256 ,5w 256 )、(3w 256 ,3w 256 )、(3w 256 ,w 256 )、 (3w 256 ,―15w 256 )、(3w 256 ,―13w 256 )、(3w 256 ,―11w 256 )、(3w 256 ,―9w 256 )、(3w 256 ,―7w 256 )、(3w 256 ,―5w 256 )、(3w 256 ,―3w 256 )、(3w 256 ,―w 256 )、 (w 256 15w 256 )、(w 256 ,13w 256 )、(w 256 ,11w 256 )、(w 256 ,9w 256 )、(w 256 ,7w 256 )、(w 256 ,5w 256 )、(w 256 ,3w 256 )、(w 256 ,w256 )、 (In 256 ,―15w 256 ),(In 256 ,―13w 256 ),(In 256 ,―11w 256 ),(In 256 ,―9w 256 ),(In 256 ,―7w 256 ),(In 256 ,―5w 256 ),(In 256 ,―3w 256 ),(In 256 ,-In 256 )、 (-15w 256 ,15in 256 )、(-15w 256 ,13w 256 )、(-15w 256 ,11in 256 )、(-15w 256 ,9w 256 )、(-15w 256 ,7w 256 )、(-15w 256 ,5w 256 )、(-15w 256 ,3in 256 )、(-15w 256 ,In 256 )、 (-15w 256 ,―15w 256 )、(-15w 256 ,―13w 256 )、(-15w 256 ,―11w 256 )、(-15w 256 ,―9w 256 )、(-15w 256 ,―7w 256 )、(-15w 256 ,―5w 256 )、(-15w 256 ,―3w 256 )、(-15w 256 ,-In 256 )、 (-13w 256 ,15in 256 )、(-13w256 ,13w 256 )、(-13w 256 ,11in 256 )、(-13w 256 ,9w 256 )、(-13w 256 ,7w 256 )、(-13w 256 ,5w 256 )、(-13w 256 ,3in 256 )、(-13 In 256 ,In 256 )、 (-13w 256 ,―15w 256 )、(-13w 256 ,―13w 256 )、(-13w 256 ,―11w 256 )、(-13w 256 ,―9w 256 )、(-13w 256 ,―7w 256 )、(-13w 256 ,―5w 256 )、(-13w 256 ,―3w 256 )、(-13w 256 ,-In 256 )、 (-11w 256 ,15in 256 )、(-11w 256 ,13w 256 )、(-11w 256 ,11in 256 )、(-11w 256 ,9w 256 )、(-11w 256 ,7w 256 )、(-11w 256 ,5w 256 )、(-11w 256 ,3in 256 )、(-11w 256 ,In 256 )、 (-11w 256 ,―15w 256 )、(-11w 256 ,―13w 256 )、(-11w 256 ,―11w256 )、(-11w 256 ,―9w 256 )、(-11w 256 ,―7w 256 )、(-11w 256 ,―5w 256 )、(-11w 256 ,―3w 256 )、(-11w 256 ,-In 256 )、 (-9w 256 ,15in 256 )、(-9w 256 ,13w 256 )、(-9w 256 ,11in 256 )、(-9w 256 ,9w 256 )、(-9w 256 ,7w 256 )、(-9w 256 ,5w 256 )、(-9w 256 ,3in 256 )、(-9w 256 ,In 256 )、 (-9w 256 ,―15w 256 )、(-9w 256 ,―13w 256 )、(-9w 256 ,―11w 256 )、(-9w 256 ,―9w 256 )、(-9w 256 ,―7w 256 )、(-9w 256 ,―5w 256 )、(-9w 256 ,―3w 256 )、(-9w 256 ,-In 256 )、 (-7w 256 ,15in 256 )、(-7w 256 ,13w 256 )、(-7w 256 ,11in 256 )、(-7w 256 ,9w 256 )、(-7w 256 ,7w256 )、(-7w 256 ,5w 256 )、(-7w 256 ,3in 256 )、(-7w 256 ,In 256 )、 (-7w 256 ,―15w 256 )、(-7w 256 ,―13w 256 )、(-7w 256 ,―11w 256 )、(-7w 256 ,―9w 256 )、(-7w 256 ,―7w 256 )、(-7w 256 ,―5w 256 )、(-7w 256 ,―3w 256 )、(-7w 256 ,-In 256 )、 (-5w 256 ,15in 256 )、(-5w 256 ,13w 256 )、(-5w 256 ,11in 256 )、(-5w 256 ,9w 256 )、(-5w 256 ,7w 256 )、(-5w 256 ,5w 256 )、(-5w 256 ,3in 256 )、(-5w 256 ,In 256 )、 (-5w 256 ,―15w 256 )、(-5w 256 ,―13w 256 )、(-5w 256 ,―11w 256 )、(-5w 256 ,―9w 256 )、(-5w 256 ,―7w 256 )、(-5w 256 ,―5w 256 )、(-5w 256 ,―3w 256 )、(-5w256 ,-In 256 )、 (-3w 256 ,15in 256 )、(-3w 256 ,13w 256 )、(-3w 256 ,11in 256 )、(-3w 256 ,9w 256 )、(-3w 256 ,7w 256 )、(-3w 256 ,5w 256 )、(-3w 256 ,3in 256 )、(-3w 256 ,In 256 )、 (-3w 256 ,―15w 256 )、(-3w 256 ,―13w 256 )、(-3w 256 ,―11w 256 )、(-3w 256 ,―9w 256 )、(-3w 256 ,―7w 256 )、(-3w 256 ,―5w 256 )、(-3w 256 ,―3w 256 )、(-3w 256 ,-In 256 )、 (-In 256 ,15in 256 ),(-In 256 ,13w 256 ),(-In 256 ,11in 256 ),(-In 256 ,9w 256 ),(-In 256 ,7w 256 ),(-In 256 ,5w 256 ),(-In 256 ,3in 256 ),(-In 256 ,In 256 )、 (-In 256 ,―15w 256 ),(-In256 ,―13w 256 ), (-w 256 ,―11w 256 ), (-w 256 ,―9w 256 ), (-w 256 ,―7w 256 ), (-w 256 ,―5w 256 ), (-w 256 ,―3w 256 ), (-w 256 ,―w 256 ), , and (w 256 is a real number greater than 0.

[0620] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, b5, b6, and b7. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), they are mapped to signal point 2001 in FIG. 20. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (15w 256 ,15w 256 )

[0621] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the bits to be transmitted (b0, b1, b2, b3, b4, b5, b6, b7). An example of the relationship between the set of b0, b1, b2, b3, b4, b5, b6, b7 (00000000 to 11111111) and the coordinates of the signal points is shown in Figure 20. The 256 signal points of 256QAM (the "circles" in Figure 20) (15w 256 ,15w 256 ), (15w 256 ,13w 256 ), (15w 256 ,11w 256 ), (15w 256 ,9w 256 ), (15w 256 ,7w 256 ), (15w 256 ,5w 256 ), (15w256 ,3in 256 )、(15w 256 ,In 256 )、 (15in 256 ,―15w 256 )、(15w 256 ,―13w 256 )、(15w 256 ,―11w 256 )、(15w 256 ,―9w 256 )、(15w 256 ,―7w 256 )、(15w 256 ,―5w 256 )、(15w 256 ,―3w 256 )、(15w 256 ,-In 256 )、 (13in 256 ,15in 256 )、(13w 256 ,13w 256 )、(13w 256 ,11in 256 )、(13w 256 ,9w 256 )、(13w 256 ,7w 256 )、(13w 256 ,5w 256 )、(13w 256 ,3in 256 )、(13w 256 ,In 256 )、 (13in 256 ,―15w 256 )、(13w 256 ,―13w 256 )、(13w 256 ,―11w 256 )、(13w 256 ,―9w 256 )、(13w 256 ,―7w 256 )、(13w 256 ,―5w 256 )、(13w 256 ,―3w 256 )、(13w 256 ,-In 256 )、 (11in 256 ,15in 256 )、(11w 256 ,13w 256 )、(11w 256 ,11in 256 )、(11w 256 ,9w 256 )、(11w 256 ,7w 256 )、(11w 256 ,5w 256 )、(11w 256 ,3in 256 )、(11w 256 ,In 256 )、 (11in 256 ,―15w 256 )、(11w 256 ,―13w 256 )、(11w 256 ,―11w 256 )、(11w 256 ,―9w 256 )、(11w 256 ,―7w 256 )、(11w 256 ,―5w 256 )、(11w 256 ,―3w 256 )、(11w 256 ,-In 256 )、 (9in 256 ,15in 256 )、(9w 256 ,13w 256 )、(9w 256 ,11 In 256 )、(9w 256 ,9w 256 )、(9w 256 ,7w 256 )、(9w 256 , 5in 256 )、(9w 256 ,3in 256 )、(9w 256 ,In 256 )、 (9in 256 ,―15w 256 )、(9w 256 ,―13w 256 )、(9w256 ,―11w 256 )、(9w 256 ,―9w 256 )、(9w 256 ,―7w 256 )、(9w 256 ,―5w 256 )、(9w 256 ,―3w 256 )、(9w 256 ,-In 256 )、 (7in 256 ,15in 256 )、(7w 256 ,13w 256 )、(7w 256 ,11in 256 )、(7w 256 ,9w 256 )、(7w 256 ,7w 256 )、(7w 256 ,5w 256 )、(7w 256 ,3in 256 )、(7w 256 ,In 256 )、 (7in 256 ,―15w 256 )、(7w 256 ,―13w 256 )、(7w 256 ,―11w 256 )、(7w 256 ,―9w 256 )、(7w 256 ,―7w 256 )、(7w 256 ,―5w 256 )、(7w 256 ,―3w 256 )、(7w 256 ,-In 256 )、 (5in 256 ,15in 256 )、(5in 256 ,13w 256 )、(5in 256 ,11in 256 )、(5in 256 ,9w 256 )、(5in 256 ,7w 256)、(5w 256 ,5w 256 )、(5w 256 ,3w 256 )、(5w 256 ,w 256 )、 (5w 256 ,―15w 256 )、(5w 256 ,―13w 256 )、(5w 256 ,―11w 256 )、(5w 256 ,―9w 256 )、(5w 256 ,―7w 256 )、(5w 256 ,―5w 256 )、(5w 256 ,―3w 256 )、(5w 256 ,―w 256 )、 (3w 256 15w 256 )、(3w 256 ,13w 256 )、(3w 256 ,11w 256 )、(3w 256 ,9w 256 )、(3w 256 ,7w 256 )、(3w 256 ,5w 256 )、(3w 256 ,3w 256 )、(3w 256 ,w 256 )、 (3w 256 ,―15w 256 )、(3w 256 ,―13w 256 )、(3w 256 ,―11w 256 )、(3w 256 ,―9w 256 )、(3w 256 ,―7w 256 )、(3w 256 ,―5w 256 )、(3w 256 ,―3w 256 )、(3w 256 ,―w 256 )、 (In 256 ,15in 256 ),(In 256 ,13w 256 ),(In 256 ,11in 256 ),(In 256 ,9w 256 ),(In 256 ,7w 256 ),(In 256 ,5w 256 ),(In 256 ,3in 256 ),(In 256 ,In 256 )、 (In 256 ,―15w 256 ),(In 256 ,―13w 256 ),(In 256 ,―11w 256 ),(In 256 ,―9w 256 ),(In 256 ,―7w 256 ),(In 256 ,―5w 256 ),(In 256 ,―3w 256 ),(In 256 ,-In 256 )、 (-15w 256 ,15in 256 )、(-15w 256 ,13w 256 )、(-15w 256 ,11in 256 )、(-15w 256 ,9w 256 )、(-15w 256 ,7w 256 )、(-15w 256 ,5w 256 )、(-15w 256 ,3in 256 )、(-15w 256 ,In 256 )、 (-15w 256 ,―15w 256 )、(-15w 256 ,―13w 256 )、(-15w 256,―11w 256 )、(-15w 256 ,―9w 256 )、(-15w 256 ,―7w 256 )、(-15w 256 ,―5w 256 )、(-15w 256 ,―3w 256 )、(-15w 256 ,-In 256 )、 (-13w 256 ,15in 256 )、(-13w 256 ,13w 256 )、(-13w 256 ,11in 256 )、(-13w 256 ,9w 256 )、(-13w 256 ,7w2 56 )、(-13w 256 ,5w 256 )、(-13w 256 ,3in 256 )、(-13w 256 ,In 256 )、 (-13w 256 ,―15w 256 )、(-13w 256 ,―13w 256 )、(-13w 256 ,―11w 256 )、(-13w 256 ,―9w 256 )、(-13w 256 ,―7w 256 )、(-13w 256 ,―5w 256 )、(-13w 256 ,―3w 256 )、(-13w 256 ,-In 256 )、 (-11w 256 ,15in 256 )、(-11w 256 ,13w 256 )、(-11w 256 ,11in 256 )、(-11w 256,9w 256 )、(-11w 256 ,7w 256 )、(-11w 256 ,5w 256 )、(-11w 256 ,3in 256 )、(-11w 256 ,In 256 )、 (-11w 256 ,―15w 256 )、(-11w 256 ,―13w 256 )、(-11w 256 ,―11w 256 )、(-11w 256 ,―9w 256 )、(-11w 256 ,―7w 256 )、(-11w 256 ,―5w 256 )、(-11w 256 ,―3w 256 )、(-11w 256 ,-In 256 )、 (-9w 256 ,15in 256 )、(-9w 256 ,13w 256 )、(-9w 256 ,11in 256 )、(-9w 256 ,9w 256 )、(-9w 256 ,7w 256 )、(-9w 256 ,5w 256 )、(-9w 256 ,3in 256 )、(-9w 256 ,In 256 )、 (-9w 256 ,―15w 256 )、(-9w 256 ,―13w 256 )、(-9w 256 ,―11w 256 )、(-9w 256 ,―9w 256 )、(-9w 256 ,―7w 256 )、(-9w 256 ,―5w256 )、(-9w 256 ,―3w 256 )、(-9w 256 ,-In 256 )、 (-7w 256 ,15in 256 )、(-7w 256 ,13w 256 )、(-7w 256 ,11in 256 )、(-7w 256 ,9w 256 )、(-7w 256 ,7w 256 )、(-7w 256 ,5w 256 )、(-7w 256 ,3in 256 )、(-7w 256 ,In 256 )、 (-7w 256 ,―15w 256 )、(-7w 256 ,―13w 256 )、(-7w 256 ,―11w 256 )、(-7w 256 ,―9w 256 )、(-7w 256 ,―7w 256 )、(-7w 256 ,―5w 256 )、(-7w 256 ,―3w 256 )、(-7w 256 ,-In 256 )、 (-5w 256 ,15in 256 )、(-5w 256 ,13w 256 )、(-5w 256 ,11in 256 )、(-5w 256 ,9w 256 )、(-5w 256 ,7w 256 )、(-5w 256 ,5w 256 )、(-5w 256 ,3in 256 )、(-5w 256 ,In 256)、 (-5w 256 ,―15w 256 )、(-5w 256 ,―13w 256 )、(-5w 256 ,―11w 256 )、(-5w 256 ,―9w 256 )、(-5w 256 ,―7w 256 )、(-5w 256 ,―5w 256 )、(-5w 256 ,―3w 256 )、(-5w 256 ,―w 256 )、 (-3w 256 15w 256 )、(-3w 256 ,13w 256 )、(-3w 256 ,11w 256 )、(-3w 256 ,9w 256 )、(-3w 256 ,7w 256 )、(-3w 256 ,5w 256 )、(-3w 256 ,3w 256 )、(-3w 256 ,w 256 )、 (-3w 256 ,―15w 256 )、(-3w 256 ,―13w 256 )、(-3w 256 ,―11w 256 )、(-3w 256 ,―9w 256 )、(-3w 256 ,―7w 256 )、(-3w 256 ,―5w 256 )、(-3w 256 ,―3w 256 )、(-3w2 56 ,―w 256 )、 (-w 256 15w 256 )、(-w256 ,13w 256 ), (-w 256 ,11w 256 ), (-w 256 ,9w 256 ), (-w 256 ,7w 256 ), (-w 256 ,5w 256 ), (-w 256 ,3w 256 ), (-w 256 ,w 256 ), (-w 256 ,―15w 256 ), (-w 256 ,―13w 256 ), (-w 256 ,―11w 256 ), (-w 256 ,―9w 256 ), (-w 256 ,―7w 256 ), (-w 256 ,―5w 256 ), (-w 256 ,―3w 256 ), (-w 256 ,―w 256 ), 20. The values ​​of the set of b0, b1, b2, b3, b4, b5, b6, and b7, 00000000 to 11111111, are shown immediately below the symbol. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") immediately above the set of b0, b1, b2, b3, b4, b5, b6, and b7, 00000000 to 11111111, represent the in-phase component I and quadrature component Q of the mapped baseband signal. Note that the relationship between the set of b0, b1, b2, b3, b4, b5, b6, and b7 (00000000 to 11111111) and the coordinates of the signal points in the case of 256QAM is not limited to that shown in FIG. The complex representation of the in-phase component I and quadrature component Q of the mapped baseband signal (in the case of 256QAM) becomes the baseband signal (s1(t) or s2(t)) in FIGS.

[0622] In this example, in Figures 5 to 7, the modulation method of baseband signal 505A (s1(t)(s1(i))) is 64QAM, and the modulation method of baseband signal 505B (s2(t)(s2(i))) is 256QAM, and the configuration of the precoding matrix will be described. In this case, it is common to make the average power of baseband signal 505A (s1(t)(s1(i))) output by mapping unit 504 in FIGS. 5 to 7 equal to the average power of baseband signal 505B (s2(t)(s2(i))). Therefore, the coefficient w 64 And the coefficient w described in the 256QAM mapping method described above 256 The following relation holds true:

[0623]

number

[0624]

number

[0625] In the formulas (S153) and (S154), z is a real number greater than 0. <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) The precoding matrix F

[0626]

number

[0627] The configuration of the above will be explained in detail below ((Example 3-1) to (Example 3-8)). (Example 3-1) The above <1> from <5> In either case, the precoding matrix F is set to one of the following:

[0628]

number

[0629] or

[0630]

number

[0631] or

[0632]

number

[0633] or

[0634]

number

[0635] In equations (S156), (S157), (S158), and (S159), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0636] When α is real:

[0637]

number

[0638] or

[0639]

number

[0640] When α is imaginary:

[0641]

number

[0642] or

[0643]

number

[0644] The modulation method for baseband signal 505A (s1(t)(s1(i))) is 64QAM, and the modulation method for baseband signal 505B (s2(t)(s2(i))) is 256QAM. Therefore, when precoding (and phase and power changes) are performed as described above and modulated signals are transmitted from each antenna, the total number of bits transmitted by the symbols transmitted from antenna 808A and antenna 808B in FIG. 8 is 1 / 256QAM, depending on the (unit) time of time u and frequency (carrier) v. ) 6 bits and (using 256QAM) 8 bits, resulting in 14 bits.

[0645] The input bits for 64QAM mapping are b0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , the input bits for 256QAM mapping are b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 When this is the case, no matter which α is set to in equation (S160), equation (S161), equation (S162), or equation (S163), In the signal z1(t)(z1(i)), (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ) exists in the in-phase I-quadrature Q plane, from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1,1,1,1,1) Similarly, for the signal z2(t)(z2(i)), (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ) exists on the in-phase I-quadrature Q plane from the signal point corresponding to (0,0,0,0,0,0,0,0,0,0,0,0,0,0,0,0) to the signal point corresponding to (1,1,1,1,1,1,1,1,1,1,1,1,1,1)

[0646] In the above, Equations (S160) to (S163) have been described as "the value of α for the receiving device to obtain good data reception quality, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8)," and this point will be explained below. In the signal z1(t)(z1(i)), (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ) corresponds to (0,0,0,0,0,0,0,0,0,0,0,0,0,0,0,0) and the signal point corresponding to (1,1,1,1,1,1,1,1,1,1,1,1,1,1) exists on the in-phase I-quadrature Q plane. 14 It is desired that the 16,384 signal points (=16,384) exist as 16,384 signal points without overlapping on the in-phase (I)-quadrature (Q) plane.

[0647] This is because, when the modulated signal transmitted from the antenna transmitting the signal z2(t)(z2(i)) does not reach the receiving device, the receiving device will perform detection and error correction decoding using the signal z1(t)(z1(i)). At this time, in order for the receiving device to obtain high data reception quality, it is desirable for there to be "16,384 signal points without overlapping." When the precoding matrix F is set to any of equations (S156), (S157), (S158), and (S159), and α is set as in equations (S160), (S161), (S162), and (S163), in the in-phase I-quadrature Q plane, for the signal u1(t)(u1(i)) described in the configuration example R1, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64, b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of constellation points in the first quadrant is as shown in Figure 21, the constellation of constellation points in the second quadrant is as shown in Figure 22, the constellation of constellation points in the third quadrant is as shown in Figure 23, and the constellation of constellation points in the fourth quadrant is as shown in Figure 24. In Figures 21, 22, 23, and 24, the horizontal axis is I, the vertical axis is Q, and "●" indicates the constellation points, and "△" indicates the origin (0).

[0648] As can be seen from Figures 21, 22, 23, and 24, there are 16,384 non-overlapping signal points on the in-phase I-quadrature Q plane. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other among the 16,380 signal points, excluding the four signal points at the top right of Figure 21, the bottom right of Figure 24, the top left of Figure 22, and the bottom left of Figure 23. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0649] Then, when the precoding matrix F is set to any one of the equations (S156), (S157), (S158), and (S159), and α is set as in the equations (S160), (S161), (S162), and (S163), in the signal u2(t) (u2(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of constellation points in the first quadrant is as shown in Figure 25, the constellation of constellation points in the second quadrant is as shown in Figure 26, the constellation of constellation points in the third quadrant is as shown in Figure 27, and the constellation of constellation points in the fourth quadrant is as shown in Figure 28. In Figures 25, 26, 27, and 28, the horizontal axis is I, the vertical axis is Q, and "●" indicates the constellation points, and "△" indicates the origin (0).

[0650] As can be seen from Figures 25, 26, 27, and 28, there are 16,384 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained in the receiving device. Let D1 be the minimum Euclidean distance among the 16,384 signal points in Figures 21, 22, 23, and 24, and D2 be the minimum Euclidean distance among the 16,384 signal points in Figures 25, 26, 27, and 28. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0651] (Example 3-2) Next, the coefficient w described in the 64QAM mapping method explained above 64 And the coefficient w described in the 256QAM mapping method described above 256 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0652]

number

[0653] or

[0654]

number

[0655] or

[0656]

number

[0657] or

[0658]

number

[0659] In equations (S164) and (S166), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0660]

number

[0661] or

[0662]

number

[0663] or

[0664]

number

[0665] or

[0666]

number

[0667] In addition, in equations (S168), (S169), (S170), and (S171), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0668]

number

[0669] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to any one of equations (S164), (S165), (S166), and (S167), and θ is set as in equations (S168), (S169), (S170), and (S171), in the same way as above, in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of constellation points in the first quadrant is as shown in Figure 21, the constellation of constellation points in the second quadrant is as shown in Figure 22, the constellation of constellation points in the third quadrant is as shown in Figure 23, and the constellation of constellation points in the fourth quadrant is as shown in Figure 24. In Figures 21, 22, 23, and 24, the horizontal axis is I, the vertical axis is Q, and "●" indicates the constellation points, and "△" indicates the origin (0).

[0670] As can be seen from Figures 21, 22, 23, and 24, there are 16,384 non-overlapping signal points on the in-phase I-quadrature Q plane. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other among the 16,380 signal points, excluding the four signal points at the top right of Figure 21, the bottom right of Figure 24, the top left of Figure 22, and the bottom left of Figure 23. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0671] Then, when the precoding matrix F is set to any one of the equations (S164), (S165), (S166), and (S167), and θ is set as in the equations (S168), (S169), (S170), and (S171), in the same way as above, in the signal u2(t) (u2(i)) described in the configuration example R1 on the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of constellation points in the first quadrant is as shown in Figure 25, the constellation of constellation points in the second quadrant is as shown in Figure 26, the constellation of constellation points in the third quadrant is as shown in Figure 27, and the constellation of constellation points in the fourth quadrant is as shown in Figure 28. In Figures 25, 26, 27, and 28, the horizontal axis is I, the vertical axis is Q, and "●" indicates the constellation points, and "△" indicates the origin (0).

[0672] As can be seen from Figures 25, 26, 27, and 28, there are 16,384 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained in the receiving device. Let D1 be the minimum Euclidean distance among the 16,384 signal points in Figures 21, 22, 23, and 24, and D2 be the minimum Euclidean distance among the 16,384 signal points in Figures 25, 26, 27, and 28. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0673] (Example 3-3) The coefficient w described in the 64QAM mapping method explained above 64 And the coefficient w described in the 256QAM mapping method described above 256 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0674]

number

[0675] or

[0676]

number

[0677] or

[0678]

number

[0679] or

[0680]

number

[0681] In equations (S173), (S174), (S175), and (S176), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0682] When α is real:

[0683]

number

[0684] or

[0685]

number

[0686] When α is imaginary:

[0687]

number

[0688] or

[0689]

number

[0690] When the precoding matrix F is set to any one of equations (S173), (S174), (S175), and (S176), and α is set as in equations (S177), (S178), (S179), and (S180), in the same way as above, in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of constellation points in the first quadrant is as shown in Figure 29, the constellation of constellation points in the second quadrant is as shown in Figure 30, the constellation of constellation points in the third quadrant is as shown in Figure 31, and the constellation of constellation points in the fourth quadrant is as shown in Figure 32. In Figures 29, 30, 31, and 32, the horizontal axis is I, the vertical axis is Q, and "●" indicates the constellation points, and "△" indicates the origin (0).

[0691] As can be seen from Figures 29, 30, 31, and 32, there are 16,384 non-overlapping signal points. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other, excluding the four signal points at the top right of Figure 29, the bottom right of Figure 32, the top left of Figure 30, and the bottom left of Figure 31. This means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0692] Then, when the precoding matrix F is set to any one of the equations (S173), (S174), (S175), and (S176), and α is set as in the equations (S177), (S178), (S179), and (S180), in the same way as above, in the signal u2(t) (u2(i)) explained in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 33, the constellation of signal points in the second quadrant is as shown in Figure 34, the constellation of signal points in the third quadrant is as shown in Figure 35, and the constellation of signal points in the fourth quadrant is as shown in Figure 36. In Figures 33, 34, 35, and 36, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0693] As can be seen from Figures 33, 34, 35, and 36, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let D1 be the minimum Euclidean distance between the 16,384 signal points in Figures 29, 30, 31, and 32, and D2 be the minimum Euclidean distance between the 16,384 signal points in Figures 33, 34, 35, and 36. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0694] (Example 3-4) Next, the coefficient w described in the 64QAM mapping method explained above 64 And the coefficient w described in the 256QAM mapping method described above 256 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0695]

number

[0696] or

[0697]

number

[0698] or

[0699]

number

[0700] or

[0701]

number

[0702] In the formulas (S181) and (S183), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z1(t) (z1(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0703]

number

[0704] or

[0705]

number

[0706] or

[0707]

number

[0708] or

[0709]

number

[0710] In addition, in equations (S185), (S186), (S187), and (S188), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0711]

number

[0712] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to any one of the formulas (S181), (S182), (S183), and (S184), and θ is set as in the formulas (S185), (S186), (S187), and (S188), in the same way as above, in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of constellation points in the first quadrant is as shown in Figure 29, the constellation of constellation points in the second quadrant is as shown in Figure 30, the constellation of constellation points in the third quadrant is as shown in Figure 31, and the constellation of constellation points in the fourth quadrant is as shown in Figure 32. In Figures 29, 30, 31, and 32, the horizontal axis is I, the vertical axis is Q, and "●" indicates the constellation points, and "△" indicates the origin (0).

[0713] As can be seen from Figures 29, 30, 31, and 32, there are 16,384 non-overlapping signal points on the in-phase I-quadrature Q plane. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other among the 16,380 signal points, excluding the four signal points at the top right of Figure 29, the bottom right of Figure 32, the top left of Figure 30, and the bottom left of Figure 31. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0714] Then, when the precoding matrix F is set to any one of the equations (S181), (S182), (S183), and (S184), and θ is set as in the equations (S185), (S186), (S187), and (S188), in the same way as above, in the signal u2(t) (u2(i)) described in the configuration example R1 on the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of signal points in the first quadrant is as shown in Figure 33, the constellation of signal points in the second quadrant is as shown in Figure 34, the constellation of signal points in the third quadrant is as shown in Figure 35, and the constellation of signal points in the fourth quadrant is as shown in Figure 36. In Figures 33, 34, 35, and 36, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0). As can be seen from Figures 33, 34, 35, and 36, there are 16,384 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained in the receiving device.

[0715] Let D1 be the minimum Euclidean distance between the 16,384 signal points in Figures 29, 30, 31, and 32, and D2 be the minimum Euclidean distance between the 16,384 signal points in Figures 33, 34, 35, and 36. Then, D1 > D2 holds. Therefore, from configuration example R1, in equations (S2), (S3), (S4), (S5), and (S8), if Q1 ≠ Q2, then Q1 > Q2 should hold.

[0716] (Example 3-5) The coefficient w described in the 64QAM mapping method explained above 64 And the coefficient w described in the 256QAM mapping method described above 256 With respect to <1> In equation (S2), P1 2 =P2 2 If <2> In equation (S3), P1 2 =P2 2 If <3> In equation (S4), P1 2 =P2 2 If <4> In the case of equation (S5) <5> In the case of equation (S8) Consider the case where the precoding matrix F when performing the above calculation is set to one of the following:

[0717]

number

[0718] or

[0719]

number

[0720] or

[0721]

number

[0722] or

[0723]

number

[0724] In equations (S190), (S191), (S192), and (S193), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0725] When α is real:

[0726]

number

[0727] or

[0728]

number

[0729] When α is imaginary:

[0730]

number

[0731] or

[0732]

number

[0733] When the precoding matrix F is set to any one of the formulas (S190), (S191), (S192), and (S193), and α is set as in the formulas (S194), (S195), (S196), and (S197), in the same way as above, in the signal u2(t) (u2(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of signal points in the first quadrant is as shown in Figure 37, the constellation of signal points in the second quadrant is as shown in Figure 38, the constellation of signal points in the third quadrant is as shown in Figure 39, and the constellation of signal points in the fourth quadrant is as shown in Figure 40. In Figures 37, 38, 39, and 40, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0734] As can be seen from Figures 37, 38, 39, and 40, there are 16,384 non-overlapping signal points. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other, excluding the four signal points at the top right of Figure 37, the bottom right of Figure 40, the top left of Figure 38, and the bottom left of Figure 39. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0735] Then, when the precoding matrix F is set to any one of the formulas (S190), (S191), (S192), and (S193), and α is set as in the formulas (S194), (S195), (S196), and (S197), in the same way as above, in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 41, the constellation of signal points in the second quadrant is as shown in Figure 42, the constellation of signal points in the third quadrant is as shown in Figure 43, and the constellation of signal points in the fourth quadrant is as shown in Figure 44. In Figures 41, 42, 43, and 44, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0736] As can be seen from FIGS. 41, 42, 43, and 44, it can be seen that there are 1024 signal points without overlapping. Therefore, there is a high possibility of obtaining high reception quality in the receiving device. Then, let the minimum Euclidean distance of the 16384 signal points in FIGS. 37, 38, 39, and 40 be D2, and the minimum Euclidean distance of the 16384 signal points in FIGS. 41, 42, 43, and 44 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0737] (Example 3-6) Next, the coefficient w described in the 64QAM mapping method described above 64 and the coefficient w described in the 256QAM mapping method described above 256 Regarding these, equations (S153) and (S154) hold, <1>In equation (S2), P1 2 = P2 2 When this is the case <2>In equation (S3), P1 2 = P2 2 When this is the case <3>In equation (S4), P1 2 = P2 2 When this is the case <4>In the case of equation (S5) <5>In the case of equation (S8) Consider the case where the precoding matrix F when performing the operations of is set to any of the following.

[0738]

Number

[0739] Or,

[0740]

number

[0741] or

[0742]

number

[0743] or

[0744]

number

[0745] In equations (S198) and (S200), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0746]

number

[0747] or

[0748]

number

[0749] or

[0750]

number

[0751] or

[0752]

number

[0753] In addition, in the formulas (S202), (S203), (S204), and (S205), tan -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0754]

number

[0755] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to any one of the formulas (S198), (S199), (S200), and (S201), and θ is set as in the formulas (S202), (S203), (S204), and (S205), in the same way as above, in the signal u2(t) (u2(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256), the constellation of signal points in the first quadrant is as shown in Figure 37, the constellation of signal points in the second quadrant is as shown in Figure 38, the constellation of signal points in the third quadrant is as shown in Figure 39, and the constellation of signal points in the fourth quadrant is as shown in Figure 40. In Figures 37, 38, 39, and 40, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0756] As can be seen from Figures 37, 38, 39, and 40, there are 16,384 non-overlapping signal points. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other, excluding the four signal points at the top right of Figure 37, the bottom right of Figure 40, the top left of Figure 38, and the bottom left of Figure 39. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0757] Then, when the precoding matrix F is set to any one of the formulas (S198), (S199), (S200), and (S201), and θ is set as in the formulas (S202), (S203), (S204), and (S205), in the same way as above, in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 41, the constellation of signal points in the second quadrant is as shown in Figure 42, the constellation of signal points in the third quadrant is as shown in Figure 43, and the constellation of signal points in the fourth quadrant is as shown in Figure 44. In Figures 41, 42, 43, and 44, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0758] As can be seen from FIGS. 41, 42, 43, and 44, it can be understood that there are 1024 signal points without overlapping. Therefore, there is a high possibility of obtaining high reception quality in the receiving device. Then, let the minimum Euclidean distance of the 16384 signal points in FIGS. 37, 38, 39, and 40 be D2, and the minimum Euclidean distance of the 16384 signal points in FIGS. 41, 42, 43, and 44 be D1. Then, D1 < D2 holds. Therefore, in the configuration example R1, when Q1 ≠ Q2 in the equations (S2), (S3), (S4), (S5), and (S8), it is preferable that Q1 < Q2 holds.

[0759] (Example 3-7) Coefficient w described in the 64QAM mapping method described above 64 And coefficient w described in the 256QAM mapping method described above 256 Regarding these, equations (S153) and (S154) hold, <1>In equation (S2), P1 2 = P2 2 When <0018​​​​​​​​​​​​​​​​​​​​​​​​​​​​​​​

number

[0763] or

[0764]

number

[0765] or

[0766]

number

[0767] In equations (S207), (S208), (S209), and (S210), α may be a real number or an imaginary number, and β may be a real number or an imaginary number. However, α is not 0 (zero). And β is also not 0 (zero). At this time, the value of α that allows the receiving device to obtain good data reception quality will be considered. Focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of α that allow the receiving device to obtain good data reception quality.

[0768] When α is real:

[0769]

number

[0770] or

[0771]

number

[0772] When α is imaginary:

[0773]

number

[0774] or

[0775]

number

[0776] When the precoding matrix F is set to any one of the equations (S207), (S208), (S209), and (S210), and α is set as in the equations (S211), (S212), (S213), and (S214), in the same way as above, in the signal u2(t) (u2(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 45, the constellation of signal points in the second quadrant is as shown in Figure 46, the constellation of signal points in the third quadrant is as shown in Figure 47, and the constellation of signal points in the fourth quadrant is as shown in Figure 48. In Figures 45, 46, 47, and 48, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0777] As can be seen from Figures 45, 46, 47, and 48, there are 16,384 non-overlapping signal points. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other, excluding the four signal points at the top right of Figure 45, the bottom right of Figure 48, the top left of Figure 46, and the bottom left of Figure 47. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0778] Then, when the precoding matrix F is set to any one of the equations (S207), (S208), (S209), and (S210), and α is set as in the equations (S211), (S212), (S213), and (S214), in the same way as above, in the signal u1(t) (u1(i)) described in the configuration example R1 in the in-phase I-quadrature Q plane, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 49, the constellation of signal points in the second quadrant is as shown in Figure 50, the constellation of signal points in the third quadrant is as shown in Figure 51, and the constellation of signal points in the fourth quadrant is as shown in Figure 52. In Figures 49, 50, 51, and 52, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal points, and "△" indicates the origin (0).

[0779] As can be seen from Figures 49, 50, 51, and 52, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let the minimum Euclidean distance of the 16,384 signal points in FIGS. 45, 46, 47, and 48 be D2, and the minimum Euclidean distance of the 16,384 signal points in FIGS. 49, 50, 51, and 52 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0780] (Example 3-8) Coefficient w described in the 64QAM mapping method explained above 64 and coefficient w described in the 256QAM mapping method explained above 256 Regarding these, equations (S153) and (S154) hold, <1>In equation (S2), when P1 2 = P2 2 <2>In equation (S3), when P1 2 = P2 2 <3>In equation (S4), when P1 2 = P2 2 <4>In the case of equation (S5) <5>In the case of equation (S8) Consider the case where the precoding matrix F when performing the operations of

[0781] [Number]

[0782] Or,

[0783] [Number] <https: / / patentscope.wipo.int / search / en / detail.jsf?docId=WO2018173244A1&recNum=

[0784] Or,

[0785] ​​​

number

[0786] or

[0787]

number

[0788] In equations (S215) and (S217), β may be a real number or an imaginary number, provided that β is not 0 (zero). At this time, the value of θ that allows the receiving device to obtain good data reception quality will be considered. First, focusing on the signal z2(t) (z2(i)) in equations (S2), (S3), (S4), (S5), and (S8), the following are the values ​​of θ that allow the receiving device to obtain good data reception quality.

[0789]

number

[0790] or

[0791]

number

[0792] or

[0793]

number

[0794] or

[0795]

number

[0796] In addition, in formulas (S219), (S220), (S221), and (S222), ta n -1 (x) is an inverse trigonometric function (the inverse function of a trigonometric function with an appropriately restricted domain of definition),

[0797]

number

[0798] Also, "tan -1 (x)" is "Tan -1 (x), "arctan(x)", or "Arctan(x)", where n is an integer. When the precoding matrix F is set to one of the equations (S215), (S216), (S217), and (S218), and θ is set as in the equations (S219), (S220), (S221), and (S222), in the same way as above, in the in-phase I-quadrature Q plane, in the signal u2(t) (u2(i)) described in the configuration example R1, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 45, the constellation of signal points in the second quadrant is as shown in Figure 46, the constellation of signal points in the third quadrant is as shown in Figure 47, and the constellation of signal points in the fourth quadrant is as shown in Figure 48. In Figures 45, 46, 47, and 48, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal point, and "△" indicates the origin (0).

[0799] As can be seen from Figures 45, 46, 47, and 48, there are 16,384 non-overlapping signal points. Furthermore, of the 16,384 signal points on the in-phase I-quadrature Q plane, the Euclidean distances between the nearest signal points are equal to each other, excluding the four signal points at the top right of Figure 45, the bottom right of Figure 48, the top left of Figure 46, and the bottom left of Figure 47. Therefore, there is a high possibility that high reception quality can be obtained in the receiving device.

[0800] Then, when the precoding matrix F is set to any one of the equations (S215), (S216), (S217), and (S218), and θ is set as in the equations (S219), (S220), (S221), and (S222), in the same way as above, in the in-phase I-quadrature Q plane, in the signal u1(t) (u1(i)) described in the configuration example R1, (b 0,64 , b 1,64 , b 2,64 , b 3,64 , b 4,64 , b 5,64 , b 0,256 , b 1,256 , b 2,256 , b 3,256 , b 4,256 , b 5,256 ,,b 6,256 , b 7,256 ), the constellation of signal points in the first quadrant is as shown in Figure 49, the constellation of signal points in the second quadrant is as shown in Figure 50, the constellation of signal points in the third quadrant is as shown in Figure 51, and the constellation of signal points in the fourth quadrant is as shown in Figure 52. In Figures 49, 50, 51, and 52, the horizontal axis is I, the vertical axis is Q, and "●" indicates the signal points, and "△" indicates the origin (0).

[0801] As can be seen from Figures 49, 50, 51, and 52, there are 1024 signal points that do not overlap, which means that there is a high possibility that high reception quality can be obtained at the receiving device. Let the minimum Euclidean distance of the 16,384 signal points in FIGS. 45, 46, 47, and 48 be D2, and the minimum Euclidean distance of the 16,384 signal points in FIGS. 49, 50, 51, and 52 be D1. Then, D1 < D2 holds. Therefore, from Configuration Example R1, in equations (S2), (S3), (S4), (S5), and (S8), when Q1 ≠ Q2, it is preferable that Q1 < Q2 holds.

[0802] (Example 3 - Supplementary) In (Examples 3 - 1) to (Examples 3 - 8), examples of the value of α and the value of θ that may obtain high data reception quality were shown. However, even if the values of α and the value of θ are not these values, high data reception quality may be obtained by satisfying the conditions shown in Configuration Example R1.

[0803] (Example 4) Hereinafter, in the mapping unit 504 of FIGS. 5 to 7, the modulation method for obtaining s1(t) (s1(i)) is 256QAM, and the modulation method for obtaining s2(t) (s2(i)) is 64QAM. For example, examples of the configuration of the precoding matrix (F) and the conditions regarding power change when performing any one of the precodings of equations (S2), (S3), (S4), (S5), and (S8), and / or power change will be described. First, the 64QAM mapping method will be described. FIG. 11 shows an example of the signal point arrangement of 64QAM in the in - phase I - quadrature Q plane. In FIG. 11, the sixty - four ○ are the signal points of 64QAM, and the horizontal axis is I and the vertical axis is Q.

[0804] The respective coordinates of the 64 signal points of 64QAM (the "○" in FIG. 11 are the signal points) in the in - phase I - quadrature Q plane are (7w 64 , 7w 64 ), (7w 64 , 5w < .004427>(7w 64 , 3w 64 ), (7w 64 , w64 )、(7w 64 ,-w 64 )、(7w 64 ,-3w 64 )、(7w 64 ,―5w 64 )、(7w 64 ,―7w 64 ) (5w 64 ,7w 64 )、(5w 64 ,5w 64 )、(5w 64 ,3w 64 )、(5w 64 ,w 64 )、(5w 64 ,-w 64 )、(5w 64 ,-3w 64 )、(5w 64 ,―5w 64 )、(5w 64 ,―7w 64 ) (3w 64 ,7w 64 )、(3w 64 ,5w 64 )、(3w 64 ,3w 64 )、(3w 64 ,w 64 )、(3w 64 ,-w 64 )、(3w 64 ,-3w 64 )、(3w 64 ,―5w 64 )、(3w 64 ,―7w 64 ) (w 64 ,7w 64 )、(w 64 ,5w 64 )、(w 64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64 ,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w 64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w 64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w 64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64), (-7w 64 ,w 64 ), (-7w 64 ,-w 64 ), (-7w 64 ,-3w 64 ), (-7w 64 ,―5w 64 ), (-7w 64 ,―7w 64 ) (w 64 is a real number greater than 0.

[0805] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, and b5. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5) = (0, 0, 0, 0, 0, 0), they are mapped to signal point 1101 in FIG. 11. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (7w 64 ,7w 64 )

[0806] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) are determined based on the bits (b0, b1, b2, b3, b4, b5) to be transmitted. An example of the relationship between the set of b0, b1, b2, b3, b4, b5 (000000 to 111111) and the coordinates of the signal points is shown in Figure 11. The 64 signal points ("○" in Figure 11) of 64QAM (7w 64 ,7w 64 ), (7w 64 ,5w 64 ), (7w 64 ,3w 64 ), (7w 64 ,w 64 ), (7w 64 ,-w 64 ), (7w 64 ,-3w 64 ), (7w 64 ,―5w 64 ), (7w 64 ,―7w 64 ) (5w 64 ,7w 64 ), (5w 64 ,5w64 )、(5w 64 ,3w 64 )、(5w 64 ,w 64 )、(5w 64 ,-w 64 )、(5w 64 ,-3w 64 )、(5w 64 ,―5w 64 )、(5w 64 ,―7w 64 ) (3w 64 ,7w 64 )、(3w 64 ,5w 64 )、(3w 64 ,3w 64 )、(3w 64 ,w 64 )、(3w 64 ,-w 64 )、(3w 64 ,-3w 64 )、(3w 64 ,―5w 64 )、(3w 64 ,―7w 64 ) (w 64 ,7w 64 )、(w 64 ,5w 64 )、(w 64 ,3w 64 )、(w 64 ,w 64 )、(w 64 ,-w 64 )、(w 64 ,-3w 64 )、(w 64 ,―5w 64 )、(w 64 ,―7w 64 ) (-w 64 ,7w 64 )、(-w 64 ,5w 64 )、(-w 64 ,3w 64 )、(-w 64 ,w 64 )、(-w 64 ,-w 64 )、(-w 64 ,-3w64 )、(-w 64 ,―5w 64 )、(-w 64 ,―7w 64 ) (-3w 64 ,7w 64 )、(-3w 64 ,5w 64 )、(-3w 64 ,3w 64 )、(-3w 64 ,w 64 )、(-3w 64 ,-w 64 )、(-3w 64 ,-3w 64 )、(-3w 64 ,―5w 64 )、(-3w 64 ,―7w 64 ) (-5w 64 ,7w 64 )、(-5w 64 ,5w 64 )、(-5w 64 ,3w 64 )、(-5w 64 ,w 64 )、(-5w 64 ,-w 64 )、(-5w 64 ,-3w 64 )、(-5w 64 ,―5w 64 )、(-5w 64 ,―7w 64 ) (-7w 64 ,7w 64 )、(-7w 64 ,5w 64 )、(-7w 64 ,3w 64 )、(-7w 64 ,w 64 )、(-7w 64 ,-w 64 )、(-7w 64 ,-3w 64 )、(-7w 64 ,―5w 64 )、(-7w 64 ,―7w 64), the values ​​of the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 are shown immediately below. The coordinates on the in-phase I-quadrature Q plane of the signal points ("○") immediately above the set 000000 to 111111 of b0, b1, b2, b3, b4, and b5 become the in-phase component I and quadrature component Q of the baseband signal after mapping. Note that the relationship between the set of b0, b1, b2, b3, b4, and b5 (000000 to 111111) and the coordinates of the signal points in the case of 64QAM is not limited to that shown in FIG. 11. The complex representation values ​​of the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 64QAM) become the baseband signal (s1(t) or s2(t)) in FIGS. 5 to 7. The mapping method for 256QAM will now be described. Figure 20 shows an example of a 256QAM signal point arrangement on the in-phase I-quadrature Q plane. In Figure 20, the 256 circles represent 256QAM signal points.

[0807] The coordinates of the 256 signal points of 256QAM (the "circles" in FIG. 20 are signal points) on the in-phase I-quadrature Q plane are as follows: (15w 256 ,15w 256 ), (15w 256 ,13w 256 ), (15w 256 ,11w 256 ), (15w 256 ,9w 256 ), (15w 256 ,7w 256 ), (15w 256 ,5w 256 ), (15w 256 ,3w 256 ), (15w 256 ,w 256 ), (15w 256 ,―15w 256 ), (15w 256 ,―13w 256 ), (15w 256 ,―11w 256 ), (15w 256 ,―9w 256 ), (15w 256 ,―7w256 )、(15w 256 ,―5w 256 )、(15w 256 ,―3w 256 )、(15w 256 ,-In 256 )、 (13in 256 ,15in 256 )、(13w 256 ,13w 256 )、(13w 256 ,11in 256 )、(13w 256 ,9w 256 )、(13w 256 ,7w 256 )、(13w 256 ,5w 256 )、(13w 256 ,3in 256 )、(13w 256 ,In 256 )、 (13in 256 ,―15w 256 )、(13w 256 ,―13w 256 )、(13w 256 ,―11w 256 )、(13w 256 ,―9w 256 )、(13w 256 ,―7w 256 )、(13w 256 ,―5w 256 )、(13w 256 ,―3w 256 )、(13w 256 ,-In 256 )、 (11in 256 ,15in 256 )、(11w 256 ,13w 256 )、(11w 256 ,11in 256 )、(11w 256 ,9w 256 )、(11w 256 ,7w 256 )、(11w 256 ,5w 256 )、(11w 256 ,3in 256)、(11w 256 ,In 256 )、 (11in 256 ,―15w 256 )、(11w 256 ,―13w 256 )、(11w 256 ,―11w 256 )、(11w 256 ,―9w 256 )、(11w 256 ,―7w 256 )、(11w 256 ,―5w 256 )、(11w 256 ,―3w 256 )、(11w 256 ,-In 256 )、 (9in 256 ,15in 256 )、(9w 256 ,13w 256 )、(9w 256 ,11in 256 )、(9w 256 ,9w 256 )、(9w 256 ,7w 256 )、(9w 256 ,5w 256 )、(9w 256 ,3in 256 )、(9w 256 ,In 256 )、 (9in 256 ,―15w 256 )、(9w 256 ,―13w 256 )、(9w 256 ,―11w 256 )、(9w 256 ,―9w 256 )、(9w 256 ,―7w 256 )、(9w 256 ,―5w 256 )、(9w 256 ,―3w 256 )、(9w 256 ,-In 256 )、 (7in 256 ,15in 256 )、(7w256 ,13w 256 )、(7w 256 ,11in 256 )、(7w 256 ,9w 256 )、(7w 256 ,7w 256 )、(7w 256 ,5w 256 )、(7w 256 ,3in 256 )、(7w 256 ,In 256 )、 (7in 256 ,―15w 256 )、(7w 256 ,―13w 256 )、(7w 256 ,―11w 256 )、(7w 256 ,―9w 256 )、(7w 256 ,―7w 256 )、(7w 256 ,―5w 256 )、(7w 256 ,―3w 256 )、(7w 256 ,-In 256 )、 (5in 256 ,15in 256 )、(5in 256 ,13w 256 )、(5in 256 ,11in 256 )、(5in 256 ,9w 256 )、(5in 256 ,7w 256 )、(5in 256 ,5w 256 )、(5in 256 ,3in 256 )、(5in 256 ,In 256 )、 (5in 256 ,―15w 256 )、(5in 256 ,―13w 256 )、(5in 256 ,―11w 256 )、(5in 256 ,―9w 256 )、(5in 256,―7w 256 )、(5 w 256 ,―5w 256 )、(5w 256 ,―3w 256 )、(5w 256 ,―w 256 )、 (3w 256 15w 256 )、(3w 256 ,13w 256 )、(3w 256 ,11w 256 )、(3w 256 ,9w 256 )、(3w 256 ,7w 256 )、(3w 256 ,5w 256 )、(3w 256 ,3w 256 )、(3w 256 ,w 256 )、 (3w 256 ,―15w 256 )、(3w 256 ,―13w 256 )、(3w 256 ,―11w 256 )、(3w 256 ,―9w 256 )、(3w 256 ,―7w 256 )、(3w 256 ,―5w 256 )、(3w 256 ,―3w 256 )、(3w 256 ,―w 256 )、 (w 256 15w 256 )、(w 256 ,13w 256 )、(w 256 ,11w 256 )、(w 256 ,9w 256 )、(w 256 ,7w 256 )、(w 256 ,5w 256 )、(w 256 ,3w 256 )、(w256 ,In 256 )、 (In 256 ,―15w 256 ),(In 256 ,―13w 256 ),(In 256 ,―11w 256 ),(In 256 ,―9w 256 ),(In 256 ,―7w 256 ),(In 256 ,―5w 256 ),(In 256 ,―3w 256 ),(In 256 ,-In 256 )、 (-15w 256 ,15in 256 )、(-15w 256 ,13w 256 )、(-15w 256 ,11in 256 )、(-15w 256 ,9w 256 )、(-15w 256 ,7w 256 )、(-15w 256 ,5w 256 )、(-15w 256 ,3in 256 )、(-15w 256 ,In 256 )、 (-15w 256 ,―15w 256 )、(-15w 256 ,―13w 256 )、(-15w 256 ,―11w 256 )、(-15w 256 ,―9w 256 )、(-15w 256 ,―7w 256 )、(-15w 256 ,―5w 256 )、(-15w 256 ,―3w 256 )、(-15w 256 ,-In 256 )、 (-13w 256 ,15in 256)、(-13w 256 ,13w 256 )、(-13w 256 ,11in 256 )、(-13w 256 ,9w 256 )、(-13w 256 ,7w 256 )、(-13w 256 ,5w 256 )、(-13w 256 ,3in 256 )、(-13w 256 ,In 256 )、 (-13w 256 ,―15w 256 )、(-13w 256 ,―13w 256 )、(-13w 256 ,―11w 256 )、(-13w 256 ,―9w 256 )、(-13w 256 ,―7w 256 )、(-13w 256 ,―5w 256 )、(-13w 256 ,―3w 256 )、(-13w 256 ,-In 256 )、 (-11w 256 ,15in 256 )、(-11w 256 ,13w 256 )、(-11w 256 ,11in 256 )、(-11w 256 ,9w 256 )、(-11w 256 ,7w 256 )、(-11w 256 ,5w 256 )、(-11w 256 ,3in 256 )、(-11w 256 ,In 256 )、 (-11w 256 ,―15w 256 )、(-11w 256 ,―13w 256 )、(-11w 256 ,―11w256 )、(-11w 256 ,―9w 256 )、(-11w 256 ,―7w 256 )、(-11w 256 ,―5w 256 )、(-11w 256 ,―3w 256 )、(-11w 256 ,-In 256 )、 (-9w 256 ,15in 256 )、(-9w 256 ,13w 256 )、(-9w 256 ,11in 256 )、(-9w 256 ,9w 256 )、(-9w 256 ,7w 256 )、(-9w 256 ,5w 256 )、(-9w 256 ,3in 256 )、(-9w 256 ,In 256 )、 (-9w 256 ,―15w 256 )、(-9w 256 ,―13w 256 )、(-9w 256 ,―11w 256 )、(-9w 256 ,―9w 256 )、(-9w 256 ,―7w 256 )、(-9w 256 ,―5w 256 )、(-9w 256 ,―3w 256 )、(-9w 256 ,-In 256 )、 (-7w 256 ,15in 256 )、(-7w 256 ,13w 256 )、(-7w 256 ,11in 256 )、(-7w 256 ,9w 256 )、(-7w256 ,7w 256 )、(-7w 256 ,5w 256 )、(-7w 256 ,3in 256 )、(-7w 256 ,In 256 )、 (-7w 256 ,―15w 256 )、(-7w 256 ,―13w 256 )、(-7w 256 ,―11w 256 )、(-7w 256 ,―9w 256 )、(-7w 256 ,―7w 256 )、(-7w 256 ,―5w 256 )、(-7w 256 ,―3w 256 )、(-7w 256 ,-In 256 )、 (-5w 256 ,15in 256 )、(-5w 256 ,13w 256 )、(-5w 256 ,11in 256 )、(-5w 256 ,9w 256 )、(-5w 256 ,7w 256 )、(-5w 256 ,5w 256 )、(-5w 256 ,3in 256 )、(-5w 256 ,In 256 )、 (-5w 256 ,―15w 256 )、(-5w 256 ,―13w 256 )、(-5w 256 ,―11w 256 )、(-5w 256 ,―9w 256 )、(-5w 256 ,―7w 256 )、(-5w 256 ,―5w 256 )、(-5w 256 ,―3w256 )、(-5w 256 ,-In 256 )、 (-3w 256 ,15in 256 )、(-3w 256 ,13w 256 )、(-3w 256 ,11in 256 )、(-3w 256 ,9w 256 )、(-3w 256 ,7w 256 )、(-3w 256 ,5w 256 )、(-3w 256 ,3in 256 )、(-3w 256 ,In 256 )、 (-3w 256 ,―15w 256 )、(-3w 256 ,―13w 256 )、(-3w 256 ,―11w 256 )、(-3w 256 ,―9w 256 )、(-3w 256 ,―7w 256 )、(-3w 256 ,―5w 256 )、(-3w 256 ,―3w 256 )、(-3w 256 ,-In 256 )、 (-In 256 ,15in 256 ),(-In 256 ,13w 256 ),(-In 256 ,11in 256 ),(-In 256 ,9w 256 ),(-In 256 ,7w 256 ),(-In 256 ,5w 256 ),(-In 256 ,3in 256 ),(-In 256 ,In 256 )、 (-In 256 ,―15w256 ), (-w 256 ,―13w 256 ), (-w 256 ,―11w 256 ), (-w 256 ,―9w 256 ), (-w 256 ,―7w 256 ), (-w 256 ,―5w 256 ), (-w 256 ,―3w 256 ), (-w 256 ,―w 256 ), , and (w 256 is a real number greater than 0.

[0808] Here, the bits to be transmitted (input bits) are assumed to be b0, b1, b2, b3, b4, b5, b6, and b7. For example, if the bits to be transmitted are (b0, b1, b2, b3, b4, b5, b6, b7) = (0, 0, 0, 0, 0, 0, 0, 0), they are mapped to signal point 2001 in FIG. 20. If the in-phase component of the baseband signal after mapping is I and the quadrature component is Q, then (I, Q) = (15w 256 ,15w 256 )

[0809] That is, the in-phase component I and quadrature component Q of the baseband signal after mapping (in the case of 256QAM) are determined based on the bits to be transmitted (b0, b1, b2, b3, b4, b5, b6, b7). An example of the relationship between the set of b0, b1, b2, b3, b4, b5, b6, b7 (00000000 to 11111111) and the coordinates of the signal points is shown in Figure 20. The 256 signal points of 256QAM (the "circles" in Figure 20) (15w 256 ,15w 256 ), (15w 256 ,13w 256 ), (15w 256 ,11w 256 ), (15w 256 ,9w 256 ), (15w 256 ,7w 256 ), (15w 256 ,5w256 )、(15w 256 ,3in 256 )、(15w 256 ,In 256 )、 (15in 256 ,―15w 256 )、(15w 256 ,―13w 256 )、(15w 256 ,―11w 256 )、(15w 256 ,―9w 256 )、(15w 256 ,―7w 256 )、(15w 256 ,―5w 256 )、(15w 256 ,―3w 256 )、(15w 256 ,-In 256 )、 (13in 256 ,15in 256 )、(13w 256 ,13w 256 )、(13w 256 ,11in 256 )、(13w 256 ,9w 256 )、(13w 256 ,7w 256 )、(13w 256 ,5w 256 )、(13w 256 ,3in 256 )、(13w 256 ,In 256 )、 (13in 256 ,―15w 256 )、(13w 256 ,―13w 256 )、(13w 256 ,―11w 256 )、(13w 256 ,―9w 256 )、(13w 256 ,―7w 256 )、(13w 256 ,―5w 256 )、(13w 256 ,―3w 256 )、(13w 256 ,-In 256 )、 (11in 256 ,15in 256 )、(11w 256 ,13w 256 )、(11w 256 ,11in 256 )、(11w 256 ,9w 256 )、(11w 256 ,7w 256 )、(11w 256 ,5w 256 )、(11w 256 ,3in 256 )、(11w 256 ,In 256 )、 (11in 256 ,―15w 256 )、(11w 256 ,―13w 256 )、(11w 256 ,―11w 256 )、(11w 256 ,―9w 256 )、(11w 256 ,―7w 256 )、(11w 256 ,―5w 256 )、(11w 256 ,―3w 256 )、(11w 256 ,-In 256 )、 (9in 256 ,15in 256 )、(9w 256 ,13w 256 )、(9w 256 ,11in 256 )、(9w 256 ,9w 256 )、(9w 256 ,7w 256 )、(9w 256 ,5w 256 )、(9w 256 ,3in 256 )、(9w 256 ,In 256 )、 (9in 256 ,―15w 256 )、(9w 256 ,―13w 256 )、(9w256 ,―11w 256 )、(9w 256 ,―9w 256 )、(9w 256 ,―7w 256 )、(9w 256 ,―5w 256 )、(9w 256 ,―3w 256 )、(9w 256 ,-In 256 )、 (7in 256 ,15in 256 )、(7w 256 ,13w 256 )、(7w 256 ,11in 256 )、(7w 256 ,9w 256 )、(7w 256 ,7w 256 )、(7w 256 ,5w 256 )、(7w 256 ,3in 256 )、(7w 256 ,In 256 )、 (7in 256 ,―15w 256 )、(7w 256 ,―13w 256 )、(7w 256 ,―11w 256 )、(7w 256 ,―9w 256 )、(7w 256 ,―7w 256 )、(7w 256 ,―5w 256 )、(7w 256 ,―3w 256 )、(7w 256 ,-In 256 )、 (5in 256 ,15in 256 )、(5in...

Claims

1. A receiving method, comprising: receiving a first group of modulation symbols and a second group of modulation symbols; the first modulation symbol group is generated by mapping first encoded data using a first 16QAM (Quadrature Amplitude Modulation) scheme, the first encoded data is generated using a first encoding scheme, a coding rate of the first encoding scheme is a first coding rate, a code length of the first encoding scheme is a first code length, and the first 16QAM scheme is a scheme designated for the first encoding scheme, the second modulation symbol group is generated by mapping second encoded data in a second 16QAM scheme, the second encoded data is generated using a second encoding scheme, a coding rate of the second encoding scheme is the first coding rate, a code length of the second encoding scheme is a second code length, a signal point arrangement of the second 16QAM scheme is different from a signal point arrangement of the first 16QAM scheme, and the second 16QAM scheme is a scheme designated for the second encoding scheme, demodulating the received first modulation symbol group based on the first 16QAM scheme and decoding the first modulation symbol group based on the first encoding scheme; demodulating the second modulation symbol group based on the second 16QAM scheme and decoding the second modulation symbol group based on the second encoding scheme; Receiving method.

2. The amplitude of the signal point closest to the origin in the signal point arrangement of the first 16QAM system is different from the amplitude of the signal point closest to the origin in the signal point arrangement of the second 16QAM system. The receiving method according to claim 1.

3. The first code length and the second code length are different, and the signal point arrangement of the first 16QAM system is different from the signal point arrangement of the second 16QAM system under the same average power condition.

2. The receiving method according to claim 1 .

4. The signal constellation of the first 16QAM system is (f #1 ×w 16a ) and the second The signal point arrangement of the 16QAM system is (f #2 ×w 16a ) and the w 16a is the coordinate value that is the condition of the average power, and #1 , said f #2 HA #1 ≠ 1 and f #2 ≠ 1 and f #1 ≠f #2 Satisfying the relationship 4. The receiving method according to claim 3.

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