Energy feedback high-power-factor air conditioner compressor driving system

Abstract

The invention belongs to the technical field of power electronics, and relates to an energy feedback high-power-factor air conditioner compressor driving system. Comprising a direct-current bus, a direct-current bus electrolytic capacitor, a motor driving circuit, a shutdown energy feedback circuit, a permanent magnet synchronous motor and a motor control module, wherein the two ends of the direct-current bus electrolytic capacitor are connected with the positive electrode and the negative electrode of the direct-current bus respectively; in the energy feedback control module for driving the combined switch device in the shutdown energy feedback circuit, the motor driving circuit and the shutdown energy feedback circuit, the second connecting end I of each phase of bridge arm is connected with the positive electrode of the direct-current bus, and the second connecting end II of each phase of bridge arm is connected with the negative electrode of the direct-current bus; the first connecting end of the phase bridge arm of the shutdown energy feedback circuit is connected with the phase power grid voltage through the phase filter inductor. The method can maintain the stability of the DC bus voltage, and reduces the influence of the power grid voltage fluctuation and the air conditioner compressor load fluctuation.

Description

Technical Field

[0001] This invention belongs to the field of power electronics technology, and more specifically, relates to an energy feedback high power factor air conditioning compressor drive system. Background Technology

[0002] In air conditioning compressor drive systems with three-phase AC input, the traditional method of establishing the DC bus voltage is to use a three-phase uncontrolled rectifier bridge to obtain a DC bus that fluctuates with the grid voltage. In some regions, where grid voltage fluctuations are large, or even in scenarios where businesses are self-powered, the DC bus voltage of the uncontrolled rectifier fluctuates significantly, which can severely affect the control of the air conditioning compressor. Simultaneously, the uncontrolled rectifier has a low input current power factor and high current distortion rate, affecting the factory qualification of the air conditioning system. Furthermore, when the air conditioning compressor is running at high speed in a deep magnetic field weakening zone, a sudden stop can cause a surge in the DC bus voltage. Excessively high voltage can damage capacitors and power switching devices, affecting the safety and reliability of the entire air conditioning system.

[0003] In home appliances such as air conditioner compressor drive systems, the power switching devices used are mostly made of silicon (Si). Power switching devices made of Si have many drawbacks, such as: low withstand voltage, making them difficult to handle AC input voltage fluctuations and DC bus voltage surges caused by compressor shutdowns at high speeds; high switching losses, resulting in low overall efficiency of the air conditioner compressor drive system; and low switching frequency, which significantly limits performance under high-speed operating conditions, making the vibration and noise of the air conditioner compressor more noticeable. Summary of the Invention

[0004] This invention addresses the problems of low switching frequency and withstand voltage, and high switching losses in existing technologies by providing an energy feedback high power factor air conditioning compressor drive system that maintains the stability of the DC bus voltage and reduces the impact of grid voltage fluctuations and air conditioning compressor load fluctuations.

[0005] This invention provides an energy feedback high power factor air conditioner compressor drive system, comprising: DC bus; The motor drive circuit is a three-phase fully symmetrical bridge circuit composed of the combined switching devices as bridge arms. The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus. Permanent magnet synchronous motor, the permanent magnet synchronous motor of Compared with the motor drive circuit The first connecting end of the phase bridge arm is connected; The motor control module is used to generate drive signals for the combined switching devices in the motor drive circuit; A shutdown energy feedback circuit, wherein the shutdown energy feedback circuit is a three-phase fully symmetrical bridge circuit composed of the combined switching devices as bridge arms. The first connecting end of the phase bridge arm is through Phase filter inductor and Phase grid voltage connection, The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus. An energy feedback control module is used to generate drive signals for the combined switching devices in the shutdown energy feedback circuit; DC bus electrolytic capacitor C dc The DC bus electrolytic capacitor is connected between the shutdown energy feedback circuit and the motor drive circuit. C dc The two ends are connected to the positive and negative terminals of the DC bus, respectively.

[0006] In some embodiments, the combined switching device includes: First connection end; The second connection end includes a second connection end I and a second connection end II; An inductor assembly includes inductor I and inductor II, wherein the first end of inductor I and the first end of inductor II are both connected to the first connection terminal; Switching circuit I, including diode I and... SiC-Mos Pipe I and SiC-Mos The first series circuit formed by connecting tubes II in series; SiC-Mos Source connection of tube I SiC-Mos The drain of tube II, SiC-Mos The drain of tube I is connected to the second connection terminal I; SiC- Mos The source of diode II is connected to the cathode of diode I. SiC-Mos The connection point between the source of diode II and the cathode of diode I is connected to the second terminal of inductor II, and the anode of diode I is connected to the second connection terminal II; Switching circuit II, including diode II and... SiC-Mos Pipe III and SiC-Mos A second series circuit formed by connecting tubes IV in series; SiC-Mos Source connection of tube III SiC-Mos The drain of tube IV, SiC-Mos The drain of diode III is connected to the anode of diode II. SiC-Mos The connection point between the drain of diode III and the anode of diode II is connected to the second terminal of inductor I; the cathode of diode II is connected to the second connection terminal I. SiC-Mos The source of tube IV is connected to the second connection terminal II.

[0007] In some embodiments, the motor control module includes: dq The axis reference voltage setpoint module obtains the value based on the system running time and switching time. d The actual rise slope of the shaft reference voltage Regarding the above d The actual rise slope of the shaft reference voltage After integration and amplitude limiting, the result is obtained d Shaft reference voltage setpoint , and given q Shaft reference voltage setpoint The value of is always 0; The angle setting module provides a ramp-up value for the reference setpoint rotational speed. n ramp The actual reference speed setpoint is obtained by limiting the amplitude. n ref Based on the actual reference speed set value n ref Calculate the reference setpoint for the electrical angle. ω eref For electrical angle reference setpoint ω eref Integrating the results yields the operating electrical angle of the air conditioner compressor. θ m Regarding the electrical angle θ m Perform trigonometric operations to obtain the sine value of the angle corresponding to the rotating coordinate system of the air conditioner compressor. θ m And cosine value cos θ m ; Two-phase voltage modulation wave conversion module I, will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ; Three-phase voltage modulation wave conversion module I converts the two-phase stationary coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system; Sine modulation module I performs per-unit processing on the three-phase voltage modulation wave to obtain the per-unitized three-phase voltage modulation wave. Based on the per-unitized three-phase voltage modulation wave and the triangular carrier wave... Zm The magnitude comparison generates the drive signal for the combined switching device in the motor drive circuit.

[0008] In some embodiments, the two-phase voltage modulation wave conversion module I will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows: d Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mαp1 , q Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mαp2 intermediate variables v mαp1 Subtract intermediate variables v mαp2 get α Axis voltage modulated wave ; d Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mβp1 , q Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mβp2 intermediate variables v mβp1 Add intermediate variables v mβp2 get β Axis voltage modulated wave .

[0009] In some embodiments, the three-phase voltage modulation wave conversion module I will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows: a Phase voltage modulation wave equal α Axis voltage modulated wave ; α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα1 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ1 ; intermediate variables v tempβ1 Subtract intermediate variables v tempα1 ,get b Phase voltage modulation wave ; intermediate variables v tempα1 Subtract the intermediate variable after taking the negative value v tempβ1 ,get c Phase voltage modulation wave .

[0010] In some embodiments, the sinusoidal modulation module I modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z m The method for generating the drive signal for the combined switching device in the motor drive circuit by comparing the magnitudes is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z m Size; like Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Pipe I S mi1 PWM drive signal mi1 and SiC-Mos Pipe II S mi2 PWM drive signal mi2 The high level is obtained by negating the high level using NOT. SiC-Mos Pipe III S mi3 PWM drive signal mi3 and SiC-Mos Pipe IV S mi4 PWM drive signal mi4Low level; like Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Pipe I S mi1 PWM drive signal mi1 and SiC-Mos Pipe II S mi2 PWM drive signal mi2 The low level is obtained by negating the low level using NOT. SiC-Mos Pipe III S mi3 PWM drive signal mi3 and SiC-Mos Pipe IV S mi4 PWM drive signal mi4 It is a high level.

[0011] In some embodiments, the drive system further includes an energy feedback control module, the energy feedback control module comprising: Two-phase voltage modulation waveform conversion module II converts the shutdown energy feedback circuit in a rotating coordinate system. d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ; Three-phase voltage modulation wave conversion module II converts the two-phase stationary coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system; Sine modulation module II performs per-unit processing on the three-phase voltage modulation wave to obtain the per-unitized three-phase voltage modulation wave. Based on the per-unitized three-phase voltage modulation wave and the triangular carrier wave... Z g The magnitude comparison generates the drive signal for the combined switching device in the shutdown energy feedback circuit.

[0012] In some embodiments, the two-phase voltage modulation wave conversion module II will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform intoα Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows: d Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gαp1 , q Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gαp2 intermediate variables v gαp1 Subtract intermediate variables v gαp2 get α Axis voltage modulated wave ,in, θ g The angle corresponding to the rotating coordinate system of the shutdown energy feedback circuit; d Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gβp1 , q Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gβp2 intermediate variables v gβp1 Add intermediate variables v gβp2 get β Axis voltage modulated wave .

[0013] In some embodiments, the three-phase voltage modulation wave conversion module II will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows: a Phase voltage modulation wave equal α Axis voltage modulated wave ; α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. vtempα2 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ2 ; intermediate variables v tempβ2 Subtract intermediate variables v tempα2 ,get b Phase voltage modulation wave ; intermediate variables v tempα2 Subtract the intermediate variable after taking the negative value v tempβ2 ,get c Phase voltage modulation wave .

[0014] In some embodiments, the sinusoidal modulation module II modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z g The method for generating the drive signal for the combined switching device in the shutdown energy feedback circuit by comparing the magnitudes is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size; like Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos Pipe I S gi1 PWM drive signal gi1 and SiC-Mos Pipe II S gi2 PWM drive signal gi2 The high level is obtained by negating the high level using NOT. SiC-Mos Pipe III S gi3 PWM drive signal gi3 and SiC-Mos Pipe IV S gi4 PWM drive signal gi4 Low level; like Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Pipe IS gi1 PWM drive signal gi1 and SiC-Mos Pipe II S gi2 PWM drive signal gi2 The low level is obtained by negating the low level using NOT. SiC-Mos Pipe III S gi3 PWM drive signal gi3 and SiC-Mos Pipe IV S gi4 PWM drive signal gi4 It is a high level.

[0015] Compared with the prior art, the advantages and positive effects of the present invention are as follows: (1) The energy feedback high power factor air conditioner compressor drive system provided by the present invention is equipped with a shutdown energy feedback circuit. Through the shutdown energy feedback circuit, the energy of DC bus voltage pumping caused by the air conditioner compressor deceleration and high speed operation is fed to the power grid, maintaining the stability of DC bus voltage, reducing the impact of power grid voltage fluctuation and air conditioner compressor load fluctuation, protecting DC bus electrolytic capacitor and power devices, improving the stability and reliability of air conditioner compressor drive system, and at the same time, energy feedback can also achieve the purpose of energy saving and consumption reduction.

[0016] (2) The energy feedback high power factor air conditioning compressor drive system provided by the present invention uses a combination switching device in both the motor drive circuit and the shutdown energy feedback circuit. The combination switching device is provided with two parallel switching circuits. In each switching circuit, two [[ID=S47]]SiC-Mos After the transistors are connected in series to form a series circuit, they are connected in series with a diode. The series connection scheme can improve the overall withstand voltage of the combined switching device, increase the circuit reliability of the combined switching device, reduce the mutual interference between the two switching circuits by adding two inductors, achieve high switching frequency and high withstand voltage, reduce switching losses, stabilize DC bus voltage, reduce the impact of grid voltage fluctuations, and improve the stability and reliability of the air conditioning compressor drive system.

[0017] (3) The energy feedback high power factor air conditioner compressor drive system provided by the present invention can actively perform power factor correction through the motor control module and the energy feedback control module, effectively reducing the input current distortion rate and improving the sinusoidal nature of the input current. Attached Figure Description

[0018] Figure 1 This is a circuit diagram of the energy feedback high power factor air conditioner compressor drive system described in an embodiment of the present invention; Figure 2 This is a circuit diagram of the combined switching device described in an embodiment of the present invention; Figure 3 In this embodiment of the invention, the output current of the motor control circuit is positive and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Conductive, SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When shut down a Phase bridge arm X a A schematic diagram of the current flow direction; Figure 4 In this embodiment of the invention, the output current of the motor control circuit is positive and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shut down SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When conducting a Phase bridge arm X a A schematic diagram of the current flow direction; Figure 5 In this embodiment of the invention, the output current of the motor control circuit is negative and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Conductive, Si-Mos Tube SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When shut down a Phase bridge arm X a A schematic diagram of the current flow direction; Figure 6 In this embodiment of the invention, the output current of the motor control circuit is negative and SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shut down SiC-Mos Tube S ma3 and SiC-Mos TubeS ma4 When conducting a Phase bridge arm X a A schematic diagram of the current flow direction; Figure 7 In this embodiment of the invention, the output current of the shutdown energy feedback circuit is positive and SiC-Mos Tube S ga1 and SiC- Mos Tube S ga2 Conductive, SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When shut down a Phase bridge arm Y a A schematic diagram of the current flow direction; Figure 8 In this embodiment of the invention, the output current of the shutdown energy feedback circuit is positive and [[ID=SS78]]SiC-Mos Tube S ga1 and SiC- Mos Tube S ga2 Shut down SiC-Mos Tube S ga3 and SiC-Mos Tube S ga4 When conducting a Phase bridge arm Y a A schematic diagram of the current flow direction; Figure 9 In this embodiment of the invention, the output current of the shutdown energy feedback circuit is negative and SS Tube S ga1 and SiC-Mos SiC- Tube S ga2 Conductive, Mos Tube S ga3 and SiC-Mos Tube S ga4 When shut down a Phase bridge arm Y a A schematic diagram of the current flow direction; SiC-Mos In this embodiment of the invention, the output current of the shutdown energy feedback circuit is negative and Figure 10 Tube Sga1 and SiC-Mos SiC- Tube S ga2 Shut down Mos Tube S ga3 and SiC-Mos Tube S ga4 When conducting a Phase bridge arm Y a A schematic diagram of the current flow direction; SiC-Mos As described in the embodiments of the present invention Figure 11 Schematic diagram of the axis reference voltage setting module; dq This is a schematic diagram of the angle setting module described in an embodiment of the present invention; Figure 12 This is a schematic diagram of the two-phase voltage modulation wave conversion module I described in an embodiment of the present invention; Figure 13 This is a schematic diagram of the three-phase voltage modulation wave conversion module I according to an embodiment of the present invention; Figure 14 This is a schematic diagram of the sinusoidal modulation module I described in an embodiment of the present invention; Figure 15 This is a schematic diagram of the two-phase voltage modulation wave conversion module II described in an embodiment of the present invention; Figure 16 This is a schematic diagram of the three-phase voltage modulation wave conversion module II according to an embodiment of the present invention; Figure 17 This is a schematic diagram of the sinusoidal modulation module II described in an embodiment of the present invention; Figure 18 For existing traditional air conditioning compressor drive systems a Schematic diagram of phase grid voltage and current waveforms; Figure 19 A schematic diagram of the DC bus voltage waveform of a conventional air conditioner compressor drive system; Figure 20 The energy feedback high power factor air conditioning compressor drive system described in this embodiment of the invention a Schematic diagram of phase grid voltage and current waveforms; Figure 21 This is a schematic diagram of the DC bus voltage waveform of the energy feedback high power factor air conditioning compressor drive system according to an embodiment of the present invention.

[0019] In the diagram, 101 is the first connection terminal, 102 is the second connection terminal I, 103 is the second connection terminal II, 200 is the DC bus, 300 is the motor drive circuit, 400 is the shutdown energy feedback circuit, 500 is the motor control module, and 501 is... Figure 22Shaft reference voltage setting module, 502; Angle setting module, 503; Two-phase voltage modulation wave transformation module I, 504; Three-phase voltage modulation wave transformation module I, 505; Sine modulation module I, 600; Energy feedback control module, 601; Two-phase voltage modulation wave transformation module II, 602; Three-phase voltage modulation wave transformation module II, 603; Sine modulation module II. Detailed Implementation

[0020] The present invention will now be described in detail with reference to the accompanying drawings through exemplary embodiments. However, it should be understood that, without further description, elements, structures, and features in one embodiment may be advantageously incorporated into other embodiments.

[0021] In the home appliance industry, existing air conditioner compressor drive systems mostly use silicon (Si) materials for their power switching devices. However, Si-based power switching devices suffer from low voltage withstand and switching frequency, high switching losses, and are unable to stabilize AC input voltage fluctuations and DC bus voltage fluctuations. This invention provides an energy-recovery high power factor air conditioner compressor drive system with a shutdown energy feedback circuit. This circuit feeds the energy generated by the air conditioner compressor slowing down or stopping at high speeds back to the power grid, maintaining DC bus voltage stability, reducing the impact of grid voltage fluctuations and air conditioner compressor load fluctuations, protecting the DC bus electrolytic capacitors and power devices, and improving the stability and reliability of the air conditioner compressor drive system. Simultaneously, energy feedback also achieves energy saving and consumption reduction.

[0022] The energy feedback high power factor air conditioning compressor drive system of the present invention will be described in detail below with reference to the accompanying drawings and embodiments.

[0023] See dq This invention provides an energy-feedback high power factor air conditioner compressor drive system, the drive system including a DC bus 200 and a DC bus electrolytic capacitor. C dc The system comprises a motor drive circuit 300, a shutdown energy feedback circuit 400, a permanent magnet synchronous motor M, a motor control module 500, and an energy feedback control module 600. The three-phase grid voltage is converted to DC voltage by the shutdown energy feedback circuit 400, and then inverted into three-phase AC voltage by the motor drive circuit 300, which is output to the permanent magnet synchronous motor M to drive its rotation, thereby driving the air conditioner compressor. When the air conditioner compressor decelerates or brakes and stops, it generates energy, which is then fed back to the DC bus 200. The shutdown energy feedback circuit 400 feeds excess energy back to the three-phase grid, preventing damage to the drive system caused by the energy generated by the air conditioner compressor. An electrolytic capacitor is also included on the DC bus. C dcThe DC bus electrolytic capacitor is connected between the shutdown energy feedback circuit and the motor drive circuit. C dc The two ends are respectively connected to the positive and negative terminals of the DC bus to stabilize the DC bus voltage. The motor drive circuit 300 is a three-phase fully symmetrical bridge circuit composed of combined switching devices as bridge arms. In the motor drive circuit 300, the second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus 200, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus 200. The permanent magnet synchronous motor M... Compared with the motor drive circuit 300 The first connecting end of the phase bridge arm is connected. The motor control module 500 is used to generate drive signals for the combined switching devices in the motor drive circuit 300. The shutdown energy feedback circuit 400 is a three-phase fully symmetrical bridge circuit composed of combined switching devices as bridge arms. The first connecting end of the phase bridge arm passes through Phase filter inductor and The phases are connected to the grid voltage. The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus 200, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus 200. The energy feedback control module 600 is used to generate drive signals for the combined switching devices in the shutdown energy feedback circuit 400.

[0024] Specifically, through large-capacity (e.g., 1000uF) DC bus electrolytic capacitors. C dc Maintain the stability of the bus voltage.

[0025] See Figure 1 The combined switching device includes: First connection terminal 101; The second connection end includes a second connection end I102 and a second connection end II103; Inductor components, including inductors L 1 and inductor L 2. Inductance L The first terminal of 1 and the inductor L The first ends of 2 are all connected to the first connection end 101; Switching circuit I, including diodes D 1 and by [[ID=SS110]]Figure 2 Tube S 1 and SiC-Mos Tube S 2. A series circuit formed by connecting two components; SiC-Mos Tube S 1 source connection SiC-Mos Tube S 2's drain, SiC-Mos TubeS The drain of 1 is connected to the second connection terminal I102; SiC-Mos Tube S 2 source-connected diode D Cathode 1, SiC-Mos Tube S 2 source and diode D The cathode connection point of 1 and the inductor L The second end of 2 is connected; diode D The anode of 1 is connected to the second connection terminal II103; Switching circuit II, including diodes D 2 and by SiC-Mos Tube S 3 and SiC-Mos Tube S 4. Series circuit formed by connecting series; SiC-Mos Tube S 3 source connection SiC-Mos Tube S 4 drain, SiC-Mos Tube S 3. Drain-connected diode D The anode of 2, SiC-Mos Tube S 3's drain and diode D The connection point of the anode of 2 with the inductor L The second terminal of 1 is connected; diode. D The cathode of 2 is connected to the second connection terminal I102. SiC-Mos Tube S The source of 4 is connected to the second connection terminal II103.

[0026] The embodiments of the present invention describe a design of two parallel switching circuits in a combined switching device, each circuit comprising two... SiC-Mos A tube and a diode, two SiC-Mos The transistors are connected in series to form a series circuit. SiC-Mos The use of tubes and series connection schemes can improve the overall withstand voltage and switching speed of combination switching devices, reduce switching losses, and increase the circuit reliability of combination switching devices. By adding two inductors, the mutual interference between the two switching circuits can be reduced, thereby increasing the reliability of the circuit.

[0027] See also [[ID=SS127]]SiC-Mos In the motor drive circuit 300, a Phase bridge arm X a Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L ma1 and inductor L ma2 Switching circuit I includes Figure 1 TubeS ma1 , SiC-Mos Tube S ma2 and diodes D ma1 Switching circuit II includes SiC-Mos Tube S ma3 , SiC-Mos Tube S ma4 and diodes D ma2 . SiC-Mos Tube S ma1 source connection SiC-Mos Tube S ma2 The drain electrode, SiC-Mos Tube S ma1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S ma2 Source-connected diode D ma1 The cathode, SiC-Mos Tube S ma2 source and diode D ma1 Cathode connection point X ma2 With inductance L ma2 Connection. Diode. D ma1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S ma3 source connection SiC-Mos Tube S ma4 The drain electrode, SiC-Mos Tube S ma3 Drain-connected diode D ma2 anode, SiC-Mos Tube S ma3 Drain and diode D ma2 anode connection point X ma1 With inductance L ma1 The second end is connected. Diode. D ma2The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S ma4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L ma1 and inductor L ma2 The first end is connected to point X ma ,point X ma Connected to the first connection end, the first connection end is connected to the permanent magnet synchronous motor M. a Connected to each other, for permanent magnet synchronous motor M a Provide a Phase voltage u ma .

[0028] b Phase bridge arm X b Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L mb1 and inductor L mb2 Switching circuit I includes SiC-Mos Tube S mb1 , SiC-Mos Tube S mb2 and diodes D mb1 Switching circuit II includes SiC-Mos Tube S mb3 , SiC-Mos Tube S mb4 and diodes D mb2 . SiC-Mos Tube S mb1 source connection SiC-Mos Tube S mb2 The drain electrode, SiC-Mos Tube S mb1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S mb2 Source-connected diode I D mb1 The cathode, SiC-Mos Tube S mb2source and diode D mb1 Cathode connection point X mb2 With Inductor II L mb2 Connection. Diode. D mb1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S mb3 source connection SiC-Mos Tube S mb4 The drain electrode, SiC-Mos Tube S mb3 Drain-connected diode D mb2 anode, SS Tube S mb3 Drain and diode D mb2 anode connection point X mb1 With inductance L mb1 The second end is connected. Diode. D mb2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S mb4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L mb1 and inductor L mb2 The first end is connected to point X mb ,point X mb Connected to the first connection end, the first connection end is connected to the permanent magnet synchronous motor M. b Connected to each other, for permanent magnet synchronous motor M b Provide b Phase voltage u mb .

[0029] c Phase bridge arm X c Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L mc1 and inductor L mc2 Switching circuit I includes SiC-Mos TubeS mc1 , SiC-Mos Tube S mc2 and diodes D mc1 Switching circuit II includes SiC-Mos Tube S mc3 , SiC-Mos Tube S mc4 and diodes D mc2 . SiC-Mos Tube S mc1 source connection SiC-Mos Tube S mc2 The drain electrode, SiC-Mos Tube S mc1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S mc2 Source-connected diode D mc1 The cathode, SiC-Mos Tube S mc2 source and diode D mc1 Cathode connection point X mc2 With inductance L mc2 Connection. Diode. D mc1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S mc3 source connection SiC-Mos Tube S mc4 The drain electrode, SiC-Mos Tube S mc3 Drain-connected diode D mc2 anode, SiC-Mos Tube S mc3 Drain and diode D mc2 anode connection point X mc1 With inductance L mc1 The second end is connected. Diode. D mc2The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. [[ID=WW168]]SiC-Mos Tube S mc4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L mc1 and inductor L mc2 The first end is connected to point X mc ,point X mc Connected to the first connection end, the first connection end is connected to the permanent magnet synchronous motor M. c Connected to each other, for permanent magnet synchronous motor M c Provide c Phase voltage u mc .

[0030] When the motor control circuit is working, the output current of the motor control circuit is alternating current. Therefore, there are four switching states for each phase bridge arm in the motor control circuit, which are described below. a Phase bridge arm X a Let's take an example to illustrate.

[0031] a Phase bridge arm X a The first connection terminal is connected to the permanent magnet synchronous motor M. a Connected, a Phase bridge arm X a The second connection terminal I is connected to the positive terminal of the DC bus. a Phase bridge arm X a The second connection terminal II is connected to the negative terminal of the DC bus.

[0032] When the output current of the motor control circuit is positive, that is, current flows out... a Phase bridge arm X a hour: See SiC-Mos ,when SiC-Mos Tube S ma1 and Figure 3 Tube S ma2 Conduction (i.e.) SiC-Mos Tube S ma1 and [[ID=17SS3]]SiC-Mos Tube S ma2 The drive signal is high level. SiC-Mos Tube Sma3 and SiC-Mos Tube S ma4 Shutdown (i.e.) SiC-Mos SiC-Mos SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is low, a Phase bridge arm X a The current is from SiC-Mos Tube S ma1 Flow direction SiC-Mos Tube S ma2 ,inductance L ma2 At this time, the current flows from the positive terminal of the DC bus to... X ma Points, Explanation X ma The potential at the point is lower than that at the positive terminal of the DC bus. This is due to the diode. D ma2 anode connection point X ma1 pass L ma1 and X ma Point connection, and diode D ma2 If the cathode of the diode is connected to the positive terminal of the DC bus, then the diode... D ma2 The anode voltage is lower than that of the diode. D ma2 The cathode voltage, thereby causing the diode D ma2 The diode will not conduct under reverse voltage, and no current will flow through it. D ma2 Due to diodes D ma1 cathode connection point X ma2 pass SiC-Mos Tube S ma2 and SiC- Mos Tube S ma1 The diode is connected to the positive terminal of the DC bus. D ma1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ma1 The anode voltage is lower than that of the diode. D ma1 The cathode voltage, thereby causing the diodeD ma1 The diode will not conduct under reverse voltage, and no current will flow through it. D ma1 .

[0033] See Figure 4 ,when SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shutdown (i.e.) SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 The drive signal is low level. SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 Conduction (i.e.) SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is high, due to the diode D ma1 The single-transistor voltage drop makes it easier for current to flow through the diode. D ma1 And flow in the opposite direction SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 The current is very small and negligible, therefore a Phase bridge arm X a The current is mainly supplied by the diode. D ma1 Flow to inductor L ma2 .

[0034] When the output current of the motor control circuit is negative, that is, when current flows in... a Phase bridge arm X a hour: See Figure 5 ,when SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Conduction (i.e.) SiC-Mos Tube S ma1 andSiC-Mos Tube S ma2 The drive signal is high level. SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 Shutdown (i.e.) SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is low, due to the diode D ma2 The single-transistor voltage drop makes it easier for current to flow through the diode. D ma2 And flow in the opposite direction SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 The current is very small and negligible. a Phase bridge arm X a The current is mainly generated by the inductance. L ma1 Flow diode D ma2 .

[0035] See Figure 6 ,when SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 Shutdown (i.e.) SiC-Mos Tube S ma1 and SiC-Mos Tube S ma2 The drive signal is low level. SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 Conduction (i.e.) SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When the drive signal is high, a Phase bridge arm X a The current is supplied by the inductor L ma1 Flow direction SiC-Mos TubeS ma3 , SiC-Mos Tube S ma4 At this time, the current is from X ma The point flows to the negative terminal of the DC bus, indicating that... X ma The potential at the point is higher than that at the negative terminal of the DC bus. This is due to the diode. D ma1 cathode connection point X ma2 Through inductance L ma2 and X ma Point connection, and diode D ma1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ma1 The anode voltage is lower than that of the diode. D ma1 The cathode voltage, thereby causing the diode D ma1 The diode will not conduct under reverse voltage, and no current will flow through it. D ma1 Due to diodes D ma2 The cathode is connected to the positive terminal of the DC bus, and the diode... D ma2 anode connection point X ma1 pass SiC-Mos Tube S ma3 and SiC-Mos Tube S ma4 When connected to the negative terminal of the DC bus, the diode... D ma2 The anode voltage is lower than that of the diode. D ma2 The cathode voltage, thereby causing the diode D ma2 The diode will not conduct under reverse voltage, and no current will flow through it. D ma2 .

[0036] In the motor control circuit, the switching transistors of each phase bridge arm are turned on or off by the drive signals generated by the motor control module.

[0037] In the shutdown energy feedback circuit 400, a Phase bridge arm Y a Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor.L ga1 and inductor L ga2 Switching circuit I includes SiC-Mos Tube S ga1 , SiC-Mos Tube S ga2 and diodes D ga1 Switching circuit II includes SiC-Mos Tube S ga3 , SiC-Mos Tube S ga4 and diodes D ga2 . SiC-Mos Tube S ga1 source connection SiC-Mos Tube S ga2 The drain electrode, SiC-Mos Tube S ga1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S ga2 Source-connected diode D ga1 The cathode, SiC-Mos Tube S ga2 source and diode D ga1 Cathode connection point X ga2 With inductance L ga2 Connection. Diode. D ga1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. SiC-Mos Tube S ga3 source connection SiC-Mos Tube S ga4 The drain electrode, SiC-Mos Tube S ga3 Drain-connected diode D ga2 anode, SiC-Mos Tube S ga3 Drain and diode D ga2 anode connection point X ga1 With inductanceL ga1 The second end is connected; diode D ga2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S ga4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L ga1 and inductor L ga2 The first end is connected to point X ga ,point X ga Connected to the first connection end, the first connection end through a Phase filter inductor L a connect a Phase grid voltage u ga .

[0038] b Phase bridge arm Y b Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L gb1 and inductor L gb2 Switching circuit I includes SiC-Mos Tube S gb1 , SiC-Mos Tube S gb2 and diodes D gb1 Switching circuit II includes SiC-Mos Tube S gb3 , SiC-Mos Tube S gb4 and diodes D gb2 . SiC-Mos Tube S gb1 source connection SiC-Mos Tube S gb2 The drain electrode, SiC-Mos Tube S gb1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. SiC-Mos Tube S gb2 Source-connected diode Dgb1 The cathode, ​ Tube S gb2 source and diode D gb1 Cathode connection point X gb2 With inductance L gb2 Connection. Diode. D gb1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. ​ Tube S gb3 source connection ​ Tube S gb4 The drain electrode, ​ Tube S gb3 Drain-connected diode D gb2 anode, ​ Tube S gb3 Drain and diode D gb2 anode connection point X gb1 With inductance L gb1 The second end is connected; diode D gb2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. ​ Tube S gb4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L gb1 and inductor L gb2 The first end is connected to point X gb ,point X gb Connected to the first connection end, the first connection end through b Phase filter inductor L b connect b Phase grid voltage u gb .

[0039] c Phase bridge arm Y c Includes a first connection terminal, a second connection terminal I, a second connection terminal II, a switching circuit I, a switching circuit II, and an inductor. L gc1and inductor L gc2 Switching circuit I includes ​ Tube S gc1 , ​ Tube S gc2 and diodes D gc1 Switching circuit II includes ​ Tube S gc3 , ​ Tube S gc4 and diodes D gc2 . ​ Tube S gc1 source connection ​ Tube S gc2 The drain electrode, ​ Tube S gc1 The drain of the first terminal is connected to the second terminal I, and the second terminal I is connected to the positive terminal of the DC bus. ​ Tube S gc2 Source-connected diode D gc1 The cathode, ​ Tube S gc2 source and diode D gc1 Cathode connection point X gc2 With inductance L gc2 Connection. Diode. D gc1 The anode is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. ​ Tube S gc3 source connection ​ Tube S gc4 The drain electrode, ​ Tube S gc3 Drain-connected diode D gc2 anode, ​ Tube S gc3 Drain and diode D gc2 anode connection point X gc1 With inductance L gc1The second end is connected; diode D gc2 The cathode is connected to the second connection terminal I, and the second connection terminal I is connected to the positive terminal of the DC bus. ​ Tube S gc4 The source terminal is connected to the second connection terminal II, and the second connection terminal II is connected to the negative terminal of the DC bus. (Inductor) L gc1 and inductor L gc2 The first end is connected to point X gc ,point X gc Connected to the first connection end, the first connection end through c Phase filter inductor L c connect c Phase grid voltage u gc .

[0040] When the shutdown energy feedback circuit is in operation, the output current of the circuit is alternating current. Therefore, there are four switching states for each phase arm of the shutdown energy feedback circuit, which are described below. a Phase bridge arm Y a Let's take an example to illustrate.

[0041] a Phase bridge arm Y a The first connection end is through a Phase filter inductor L a connect a Phase grid voltage u ga , a Phase bridge arm Y a The second connection terminal I is connected to the positive terminal of the DC bus. a Phase bridge arm Y a The second connection terminal II is connected to the negative terminal of the DC bus.

[0042] When the output current of the shutdown energy feedback circuit is positive, that is, current flows out... a Phase bridge arm Y a hour: See ​ ,when ​ Tube S ga1 and ​ Tube S ga2 Conduction (i.e.) ​ TubeS ga1 and ​ Tube S ga2 The drive signal is high level. ​ Tube S ga3 and ​ Tube S ga4 Shutdown (i.e.) ​ Tube S ga3 and ​ Tube S ga4 When the drive signal is low, a Phase bridge arm Y a The current is from ​ Tube S ga1 Flow direction ​ Tube S ga2 ,inductance L ga2 At this time, the current flows from the positive terminal of the DC bus to... X ga Points, Explanation X ga The potential at the point is lower than that at the positive terminal of the DC bus. This is due to the diode. D ga2 anode connection point X ga1 Through inductance L ga1 and X ga Point connection, and diode D ga2 If the cathode of the diode is connected to the positive terminal of the DC bus, then the diode... D ga2 The anode voltage is lower than that of the diode. D ga2 The cathode voltage, thereby causing the diode D ga2 The diode will not conduct under reverse voltage, and no current will flow through it. D ga2 Due to diodes D ga1 cathode connection point X ga2 pass ​ Tube S ga2 and ​ Tube S ga1 The diode is connected to the positive terminal of the DC bus. D ga1If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ga1 The anode voltage is lower than that of the diode. D ga1 The cathode voltage, thereby causing the diode D ga1 The diode will not conduct under reverse voltage, and no current will flow through it. D ga1 .

[0043] See ​ ,when ​ Tube S ga1 and ​ Tube S ga2 Shutdown (i.e.) ​ Tube S ga1 and ​ Tube S ga2 The drive signal is low level. ​ Tube S ga3 and ​ Tube S ga4 Conduction (i.e.) ​ Tube S ga3 and ​ Tube S ga4 When the drive signal is high, due to the diode D ga1 The single-transistor voltage drop makes it easier for current to flow through the diode. D ga1 And flow in the opposite direction ​ Tube S ga3 and ​ Tube S ga4 The current is very small and negligible, therefore a Phase bridge arm Y a The current is mainly supplied by the diode. D ga1 Flow to inductor L ga2 .

[0044] When the output current of the shutdown energy feedback circuit is negative, that is, current flows into... a Phase bridge arm Y a hour: See ​ ,when ​ Tube Sga1 and ​ Tube S ga2 Conduction (i.e.) ​ Tube S ga1 and ​ Tube S ga2 The drive signal is high level. ​ Tube S ga3 and ​ Tube S ga4 Shutdown (i.e.) ​ Tube S ga3 and ​ Tube S ga4 When the drive signal is low, due to the diode D ga2 The single-transistor voltage drop makes it easier for current to flow through the diode. D ga2 And flow in the opposite direction ​ Tube S ga1 and ​ Tube S ga2 The current is very small and negligible. a Phase bridge arm Y a The current is mainly generated by the inductance. L ga1 Flow diode D ga2 .

[0045] See ​ ,when ​ Tube S ga1 and ​ Tube S ga2 Shutdown (i.e.) ​ Tube S ga1 and ​ Tube S ga2 The drive signal is low level. ​ Tube S ga3 and ​ Tube S ga4 Conduction (i.e.) ​ Tube S ga3 and ​ Tube S ga4When the drive signal is high, a Phase bridge arm Y a The current is supplied by the inductor L ga1 Flow direction ​ Tube S ga3 , ​ Tube S ga4 At this time, the current is from X ga The point flows to the negative terminal of the DC bus, indicating that... X ga The potential at the point is higher than that at the negative terminal of the DC bus. This is due to the diode. D ga1 cathode connection point X ga2 Through inductance L ga2 and X ga Point connection, and diode D ga1 If the anode of the diode is connected to the negative terminal of the DC bus, then the diode... D ga1 The anode voltage is lower than that of the diode. D ga1 The cathode voltage, thereby causing the diode D ga1 The diode will not conduct under reverse voltage, and no current will flow through it. D ga1 Due to diodes D ga2 The cathode is connected to the positive terminal of the DC bus, and the diode... D ga2 anode connection point X ga1 pass ​ Tube S ga3 and ​ Tube S ga4 When connected to the negative terminal of the DC bus, the diode... D ga2 The anode voltage is lower than that of the diode. D ga2 The cathode voltage, thereby causing the diode D ga2 The diode will not conduct under reverse voltage, and no current will flow through it. D ga2 .

[0046] In the shutdown energy feedback circuit, the switching transistors of each phase bridge arm are turned on or off by drive signals generated by the energy feedback control module.

[0047] Specifically, in some embodiments, the combined switching devices used in the motor drive circuit and the shutdown energy feedback circuit are... ​ - ​ The tube is 600V ​ - ​ Tube.

[0048] In some embodiments, see continue to see ​ The motor control module 500 includes: ​ The shaft reference voltage setpoint module 501 obtains the value based on the system running time and switching time. d The actual rise slope of the shaft reference voltage Regarding the above d The actual rise slope of the shaft reference voltage After integration and amplitude limiting, the result is obtained d Shaft reference voltage setpoint , and given q Shaft reference voltage setpoint The value of is always 0; Angle setting module 502, ramping up the reference setpoint for rotational speed. n ramp The actual reference speed setpoint is obtained by limiting the amplitude. n ref Based on the actual reference speed set value n ref Calculate the reference setpoint for the electrical angle. ​ eref For electrical angle reference setpoint ​ eref Integrating the results yields the operating electrical angle of the air conditioner compressor. ​ m Regarding the electrical angle ​ m Perform trigonometric operations to obtain the sine value of the angle corresponding to the rotating coordinate system of the air conditioner compressor. ​ m And cosine value cos ​ m ; Two-phase voltage modulation wave conversion module I503, will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ; The three-phase voltage modulation wave conversion module I504 converts the two-phase static coordinate system...α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system; The sinusoidal modulation module I505 normalizes the three-phase voltage modulation wave to obtain a normalized three-phase voltage modulation wave. Based on the normalized three-phase voltage modulation wave and the triangular carrier wave... Z m The magnitude comparison generates the drive signal for the combined switching device in the motor drive circuit.

[0049] ​ The shaft reference voltage setpoint module 501 determines the voltage based on the system running time and switching time. d The actual slope of the shaft reference voltage is obtained by integrating and then limiting it. d The shaft reference voltage is set to a specific value. This method effectively controls the motor's starting process, ensuring a smooth current rise during startup and preventing shocks to the motor and power grid caused by sudden current changes. Simultaneously, it will... q The shaft reference voltage setpoint is kept constant at 0, which helps simplify the control logic and ensures that the motor mainly operates under load during the initial startup phase. d The shaft voltage is controlled to achieve more precise start-up control.

[0050] It should be noted that the system running time refers to the time from when the drive system's power is turned on and the output drive signal PWM begins to be output, until control stops and the drive signal PWM is no longer output. The switching time refers to the time after the drive system starts outputting the drive signal PWM, waiting for the energy feedback control module 600 to control the DC bus voltage to reach a suitable value (e.g., 530V). After the switching time, the given motor control module 500... ​ Shaft reference voltage to prevent a sudden drop in bus voltage caused by synchronous motor starting by the motor control module 500.

[0051] The angle setting module 502 limits the ramp-up value of the speed reference setpoint to obtain the actual reference speed setpoint, and calculates the electrical angle reference setpoint accordingly, thereby obtaining the operating electrical angle of the air conditioning compressor. This processing method can ensure a smooth increase in motor speed, avoid mechanical stress and current fluctuations caused by excessively rapid speed changes, and thus improve the stability and reliability of motor operation.

[0052] Two-phase voltage modulation wave conversion module I503 will d shaft and q The shaft reference voltage setpoint is transformed into a two-phase stationary coordinate system. α shaft and βThe shaft voltage modulation wave and three-phase voltage modulation wave transformation module I504 further transform the voltage modulation wave in the two-phase stationary coordinate system into a three-phase voltage modulation wave in the three-phase stationary coordinate system. This transformation process enables precise control of the motor voltage, resulting in a more reasonable voltage distribution and improved motor operating efficiency and power factor.

[0053] The sinusoidal modulation module I505 normalizes the three-phase voltage modulation wave and generates the drive signal for the combined switching devices in the motor drive circuit by comparing the magnitude of the normalized three-phase voltage modulation wave with that of the triangular carrier wave. This modulation method can further optimize the voltage control of the motor, actively perform power factor correction, reduce harmonic content, effectively reduce the input current distortion rate, make the motor current waveform closer to a sine wave, reduce electromagnetic interference and noise of the motor, and improve the operating quality of the motor.

[0054] In some embodiments, see ​ , ​ The shaft reference voltage setting module is based on the system running time. ​ With switching time T on The size is obtained d The actual rise slope of the shaft reference voltage The method is as follows: Compare system runtime ​ With switching time T on Size; If system uptime ​ Greater than the switching time T on ,but d The actual slope of the shaft reference voltage is... d The rising slope of the reference voltage on the axis V slope If the system uptime ​ Less than switching time T on ,but d The actual slope of the shaft reference voltage is 0.

[0055] In some embodiments, see ​ The angle setting module sets the value based on the actual reference rotational speed. n ref Calculate the reference setpoint for the electrical angle. ​ eref The method is as follows: Set the actual reference speed value n ref Multiply by 2 × π / 60 to obtain the reference value of the mechanical angular velocity. ​ mref ; Mechanical angular velocity reference setpoint ​ mref Multiply by permanent magnet series ​ Divide by 2 to get the electrical angle reference value. ​ eref .

[0056] In some embodiments, see ​ The two-phase voltage modulation wave conversion module I will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows: d Shaft reference voltage setpoint cos ​ m Obtain intermediate variables v mαp1 , q Shaft reference voltage setpoint Multiply by sin ​ m Obtain intermediate variables v mαp2 intermediate variables v mαp1 Subtract intermediate variables v mαp2 get α Axis voltage modulated wave ; d Shaft reference voltage setpoint Multiply by sin ​ m Obtain intermediate variables v mβp1 , q Shaft reference voltage setpoint cos ​ m Obtain intermediate variables v mβp2 intermediate variables v mβp1 Add intermediate variables v mβp2 get β Axis voltage modulated wave .

[0057] In some embodiments, see ​ The three-phase voltage modulation wave conversion module I will αAxis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows: a Phase voltage modulation wave equal α Axis voltage modulated wave ; α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα1 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ1 ; intermediate variables v tempβ1 Subtract intermediate variables v tempα1 ,get b Phase voltage modulation wave ; intermediate variables v tempα1 Subtract the intermediate variable after taking the negative value v tempβ1 ,get c Phase voltage modulation wave .

[0058] In some embodiments, see ​ The method by which the sinusoidal modulation module I normalizes the three-phase voltage modulation wave to obtain the normalized three-phase voltage modulation wave is as follows: ... a Phase voltage modulation wave 、b Phase voltage modulation wave , c Phase voltage modulation wave Divide by V dc / 2 is normalized a Phase voltage modulation wave Standardized b Phase voltage modulation wave Standardized c Phase voltage modulation wave .

[0059] In some embodiments, the sinusoidal modulation module I modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z m The method for generating the drive signal for the combined switching device in the motor drive circuit by comparing the magnitudes is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z m Size; like Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. ​ Tube S mi1 PWM drive signal mi1 and ​ Tube S mi2 PWM drive signal mi2 The high level is obtained by negating the high level using NOT. ​ Tube S mi3 PWM drive signal mi3 and ​ Tube S mi4 PWM drive signal mi4 Low level; like Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. ​ Tube S mi1 PWM drive signal mi1 and ​ Tube S mi2 PWM drive signal mi2 The low level is obtained by negating the low level using NOT. ​ Tube S mi3 PWM drive signal mi3 and SiC-Mos Tube S mi4 PWM drive signal mi4 It is a high level.

[0060] Specifically, in some embodiments, triangular carriers Z m It is a triangular carrier with a maximum value of 1, a minimum value of -1, and a width of 50μs.

[0061] Specifically, in some embodiments, see further details. Figure 15 Generate the motor drive circuit a The method for driving signals for phase bridge arm combination switching devices is as follows: The normalized parts are compared using a comparator. a Phase voltage modulation wave With triangular carrier Z m Size; like a Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S ma1 PWM drive signal ma1 and SiC-Mos Tube S ma2 PWM drive signal ma2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S ma3 PWM drive signal ma3 and SiC-Mos Tube S ma4 PWM drive signal ma4 Low level; like a Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S ma1 PWM drive signal ma1 and SiC-Mos Tube S ma2 PWM drive signal ma2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S ma3 PWM drive signal ma3 and SiC-Mos Tube S ma4 PWM drive signal ma4 It is a high level.

[0062] In some embodiments, see continue to see Figure 15 Generate the motor drive circuit b The method for driving signals for phase bridge arm combination switching devices is as follows: The normalized parts are compared using a comparator. b Phase voltage modulation wave With triangular carrier Z mSize; like b Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S mb1 PWM drive signal mb1 and SiC-Mos Tube S mb2 PWM drive signal mb2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S mb3 PWM drive signal mb3 and SiC-Mos Tube S mb4 PWM drive signal mb4 Low level; like b Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S mb1 PWM drive signal mb1 and SiC-Mos Tube S mb2 PWM drive signal mb2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S mb3 PWM drive signal mb3 and SiC-Mos Tube S mb4 PWM drive signal mb4 It is a high level.

[0063] In some embodiments, see continue to see Figure 15 Generate the motor drive circuit c The method for driving signals for phase bridge arm combination switching devices is as follows: The normalized parts are compared using a comparator. c Phase voltage modulation wave With triangular carrier Z m Size; like c Phase voltage modulation wave Greater than or equal to triangular carrier Z mWhen the comparator outputs a high level, the result is obtained. SiC-Mos Tube S mc1 PWM drive signal mc1 and SiC-Mos Tube S mc2 PWM drive signal mc2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S mc3 PWM drive signal mc3 and SiC-Mos Tube S mc4 PWM drive signal mc4 Low level; like c Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S mc1 PWM drive signal mc1 and SiC-Mos Tube S mc2 PWM drive signal mc2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S mc3 PWM drive signal mc3 and SiC-Mos Tube S mc4 PWM drive signal mc4 It is a high level.

[0064] In some embodiments, see continue to see Figure 1 The energy feedback control module 600 includes: The two-phase voltage modulation waveform conversion module II601 converts the shutdown energy feedback circuit in a rotating coordinate system. d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ; The three-phase voltage modulation wave conversion module II602 converts the two-phase static coordinate system into a single phase voltage modulation wave. α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system; The sinusoidal modulation module II 603 normalizes the three-phase voltage modulation wave to obtain a normalized three-phase voltage modulation wave. Based on the normalized three-phase voltage modulation wave and the triangular carrier wave... Z g The magnitude comparison generates the drive signal for the combined switching device in the shutdown energy feedback circuit.

[0065] In some embodiments, see Figure 16 The two-phase voltage modulation wave conversion module II will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows: d Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gαp1 , q Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gαp2 intermediate variables v gαp1 Subtract intermediate variables v gαp2 get α Axis voltage modulated wave ,in, θ g The angle corresponding to the rotating coordinate system of the shutdown energy feedback circuit; d Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gβp1 , q Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gβp2 intermediate variables v gβp1 Add intermediate variables v gβp2 get βAxis voltage modulated wave .

[0066] In some embodiments, see Figure 17 The three-phase voltage modulation wave conversion module II will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows: a Phase voltage modulation wave equal α Axis voltage modulated wave ; α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα2 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ2 ; intermediate variables v tempβ2 Subtract intermediate variables v tempα2 ,get b Phase voltage modulation wave ; intermediate variables v tempα2 Subtract the intermediate variable after taking the negative value v tempβ2 ,get c Phase voltage modulation wave .

[0067] Specifically, see Figure 18 The method by which the sinusoidal modulation module II normalizes the three-phase voltage modulation wave to obtain the normalized three-phase voltage modulation wave is as follows: The sinusoidal modulation module II normally processes the three-phase voltage modulation wave to obtain the normalized three-phase voltage modulation wave. a Phase voltage modulation wave 、b Phase voltage modulation wave , c Phase voltage modulation wave Divide by V dc / 2 is normalized a Phase voltage modulation wave Standardized b Phase voltage modulation wave Standardized c Phase voltage modulation wave .

[0068] In some embodiments, the sinusoidal modulation module II modulates the three-phase voltage modulation wave after standardization with a triangular carrier wave. Z g The method for generating the drive signal for the combined switching device in the shutdown energy feedback circuit by comparing the magnitudes is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size; like Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S gi1 PWM drive signal gi1 and SiC-Mos Tube S gi2 PWM drive signal gi2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S gi3 PWM drive signal gi3 and SiC-Mos Tube S gi4 PWM drive signal gi4 Low level; like Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S gi1 PWM drive signal gi1 and Tube S gi2 PWM drive signal gi2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S gi3 PWM drive signal gi3 and Tube S gi4 PWM drive signal gi4 It is a high level.

[0069] Specifically, in some embodiments, triangular carriers Z gIt is a triangular carrier with a maximum value of 1, a minimum value of -1, and a width of 50μs.

[0070] Specifically, in some embodiments, see further details. SiC-Mos In the shutdown energy feedback circuit a The method for driving signals for phase bridge arm combination switching devices is as follows: The normalized parts are compared using a comparator. a Phase voltage modulation wave With triangular carrier Z g Size; like a Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. Tube S ga1 PWM drive signal ga1 and SiC-Mos Tube S ga2 PWM drive signal ga2 The high level is obtained by negating the high level using NOT. Tube S ga3 PWM drive signal ga3 and Figure 18 Tube S ga4 PWM drive signal ga4 Low level; like a Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. Tube S ga1 PWM drive signal ga1 and SiC-Mos Tube S ga2 PWM drive signal ga2 The low level is obtained by negating the low level using NOT. Tube S ga3 PWM drive signal ga3 and SiC-Mos Tube S ga4 PWM drive signal ga4 It is a high level.

[0071] Specifically, in some embodiments, see further details. In the shutdown energy feedback circuit b The method for driving signals for phase bridge arm combination switching devices is as follows: The normalized parts are compared using a comparator. b Phase voltage modulation wave With triangular carrier Z g Size; like b Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos Tube S gb1 PWM drive signal gb1 and Tube S gb2 PWM drive signal gb2 The high level is obtained by negating the high level using NOT. SiC-Mos Tube S gb3 PWM drive signal gb3 and Tube S gb4 PWM drive signal gb4 Low level; like b Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Tube S gb1 PWM drive signal gb1 and Tube S gb2 PWM drive signal gb2 The low level is obtained by negating the low level using NOT. SiC-Mos Tube S gb3 PWM drive signal gb3 and Tube S gb4 PWM drive signal gb4 It is a high level.

[0072] Specifically, in some embodiments, see further details. SiC-Mos In the shutdown energy feedback circuit, c The method for driving signals for phase bridge arm combination switching devices is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size; like c Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. Tube S gc1 PWM drive signal gc1 and SiC-Mos Tube S gc2 PWM drive signal gc2 The high level is obtained by negating the high level using NOT. Tube S gc3 PWM drive signal gc3 and Figure 18 Tube S gc4 PWM drive signal gc4 Low level; like c Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. Tube S gc1 PWM drive signal gc1 and SiC-Mos Tube S gc2 PWM drive signal gc2 The low level is obtained by negating the low level using NOT. Tube S gc3 PWM drive signal gc3 and SiC-Mos Tube S gc4 PWM drive signal gc4 It is a high level.

[0073] To verify the effectiveness of the energy feedback high power factor air conditioner compressor drive system described above, a simulation model was built using Simulink for verification.

[0074] A simulation model of an energy-feedback high power factor air conditioner compressor drive system was built in Simulink. The effective value of the three-phase power grid line voltage is 380V, and the three-phase filter inductors are... L a , L b ,L c All are 2mH DC bus electrolytic capacitors C dc The parameters of the 1000μF permanent magnet synchronous motor M are as follows: stator resistance 0.63Ω, direct-axis inductance 0.00268H, quadrature-axis inductance 0.00347H, flux linkage 0.42Wb, and moment of inertia 0.0057kg / m. 2 The number of pole pairs is 3, and the motor speed is set to 1000 r / min. The energy feedback control module... d Shaft reference voltage setpoint Set to 310V. q Shaft reference voltage setpoint Set to 2V, the corresponding angle of the rotating coordinate system of the shutdown energy feedback circuit. g The frequency is set to 314.16 rad / s, and the initial phase is -1.5708 rad; in the motor control module, SiC-Mos Shaft reference voltage given module d The rising slope of the reference voltage on the axis V slope Set to 1552.9V / s, switching time T on Set to 0.002s, the integrator's limit is 132V; the ramp-up value of the speed reference setpoint in the angle setpoint module. n ramp The limiter is set to 11765 r / (min·s), with an upper limit of 1000 r / min and a lower limit of 0 r / min. For traditional air conditioning compressor drive systems a The phase grid voltage and current, and the grid current input to the entire system are sawtooth-shaped pulses with a high distortion rate, resulting in a very low power factor; from SiC-Mos It can also be seen that the DC bus voltage of the traditional air conditioning compressor drive system fluctuates greatly, which is not conducive to stable and high-performance air conditioning compressor control. The grid voltage and current waveforms of the high power factor air conditioning compressor drive system with energy feedback function proposed in this invention are shown. The grid voltage and current are in phase, the power factor is very high, close to 1, and the grid current has a high sinusoidal degree. SiC-Mos SiC-Mos SiC-Mos SiC-Mos Figure 18 SiC-Mos SiC-Mos [[ID=6 It can be seen that the DC bus voltage of the energy-feedback high power factor air conditioning compressor system proposed in this invention is relatively stable, which is beneficial to the stable and high-performance control of the air conditioning compressor. The above results demonstrate the effectiveness of the energy-feedback high power factor air conditioning compressor drive system described in this invention.

[0075] The above embodiments are used to explain the present invention, but not to limit the present invention. Any modifications and changes made to the present invention within the spirit and scope of the claims shall fall within the protection scope of the present invention.

Claims

1. A high power factor air conditioning compressor drive system with energy feedback, characterized in that, include: DC bus; The motor drive circuit is a three-phase fully symmetrical bridge circuit composed of combination switching devices as bridge arms. The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus. Permanent magnet synchronous motor, the permanent magnet synchronous motor of Compared with the motor drive circuit The first connecting end of the phase bridge arm is connected; The motor control module is used to generate drive signals for the combined switching devices in the motor drive circuit; The shutdown energy feedback circuit is a three-phase fully symmetrical bridge circuit composed of the combined switching devices as bridge arms. The first connecting end of the phase bridge arm passes through Phase filter inductor and Phase grid voltage connection, The second connection terminal I of each phase bridge arm is connected to the positive terminal of the DC bus, and the second connection terminal II of each phase bridge arm is connected to the negative terminal of the DC bus. An energy feedback control module is used to generate drive signals for the combined switching devices in the shutdown energy feedback circuit; DC bus electrolytic capacitor C dc The DC bus electrolytic capacitor is connected between the shutdown energy feedback circuit and the motor drive circuit. C dc The two ends are connected to the positive and negative terminals of the DC bus, respectively.

2. The energy feedback high power factor air conditioning compressor drive system as described in claim 1, characterized in that, The combined switching device includes: First connection end; The second connection end includes a second connection end I and a second connection end II; An inductor assembly includes inductor I and inductor II, wherein the first end of inductor I and the first end of inductor II are both connected to the first connection terminal; Switching circuit I, including diode I and... SiC-Mos Pipe I and SiC-Mos The first series circuit formed by connecting tubes II in series; SiC-Mos Source connection of tube I SiC-Mos The drain of tube II, SiC-Mos The drain of tube I is connected to the second connection terminal I; SiC-Mos The source of diode II is connected to the cathode of diode I. SiC-Mos The connection point between the source of diode II and the cathode of diode I is connected to the second terminal of inductor II, and the anode of diode I is connected to the second connection terminal II; Switching circuit II, including diode II and... SiC-Mos Pipe III and SiC-Mos A second series circuit formed by connecting tubes IV in series; SiC-Mos Source connection of tube III SiC-Mos The drain of tube IV, SiC-Mos The drain of diode III is connected to the anode of diode II. SiC-Mos The connection point between the drain of diode III and the anode of diode II is connected to the second terminal of inductor I; the cathode of diode II is connected to the second connection terminal I. SiC-Mos The source of tube IV is connected to the second connection terminal II.

3. The energy feedback high power factor air conditioning compressor drive system as described in claim 1, characterized in that, The motor control module includes: dq The axis reference voltage setpoint module obtains the value based on the system running time and switching time. d The actual slope of the shaft reference voltage Regarding the above d The actual slope of the shaft reference voltage After integration and amplitude limiting, the result is obtained d Shaft reference voltage setpoint , and given q Shaft reference voltage setpoint The value of is always 0; The angle setting module provides a ramp-up value for the reference setpoint rotational speed. n ramp The actual reference speed setpoint is obtained by limiting the amplitude. n ref Based on the actual reference speed set value n ref Calculate the reference setpoint for the electrical angle. ω eref For electrical angle reference setpoint ω eref Integrating the results yields the operating electrical angle of the air conditioner compressor. θ m Regarding the electrical angle θ m Perform trigonometric operations to obtain the sine value of the angle corresponding to the rotating coordinate system of the air conditioner compressor. θ m And cosine value cos θ m ; Two-phase voltage modulation wave conversion module I, will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ; Three-phase voltage modulation wave conversion module I converts the two-phase stationary coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system; Sine modulation module I performs per-unit processing on the three-phase voltage modulation wave to obtain the per-unitized three-phase voltage modulation wave. Based on the per-unitized three-phase voltage modulation wave and the triangular carrier wave... Z m The magnitude comparison generates the drive signal for the combined switching device in the motor drive circuit.

4. The energy feedback high power factor air conditioning compressor drive system as described in claim 3, characterized in that, The two-phase voltage modulation wave conversion module I will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows: d Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mαp1 , q Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mαp2 intermediate variables v mαp1 Subtract intermediate variables v mαp2 get α Axis voltage modulated wave ; d Shaft reference voltage setpoint Multiply by sin θ m Obtain intermediate variables v mβp1 , q Shaft reference voltage setpoint cos θ m Obtain intermediate variables v mβp2 intermediate variables v mβp1 Add intermediate variables v mβp2 get β Axis voltage modulated wave .

5. The energy feedback high power factor air conditioning compressor drive system as described in claim 3, characterized in that, The three-phase voltage modulation wave conversion module I will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows: a Phase voltage modulation wave equal α Axis voltage modulated wave ; α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα1 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ1 ; intermediate variables v tempβ1 Subtract intermediate variables v tempα1 ,get b Phase voltage modulation wave ; intermediate variables v tempα1 Subtract the intermediate variable after taking the negative value v tempβ1 ,get c Phase voltage modulation wave .

6. The energy feedback high power factor air conditioning compressor drive system as described in claim 3, characterized in that, The sinusoidal modulation module I modulates the normalized three-phase voltage modulation wave with a triangular carrier wave. Z m The method for generating the drive signal for the combined switching device in the motor drive circuit by comparing the magnitudes is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z m Size; like Phase voltage modulation wave Greater than or equal to triangular carrier Z m When the comparator outputs a high level, the result is obtained. SiC-Mos Pipe I S mi1 PWM drive signal mi1 and SiC-Mos Pipe II S mi2 PWM drive signal mi2 The high level is obtained by negating the high level using NOT. SiC-Mos Pipe III S mi3 PWM drive signal mi3 and SiC-Mos Pipe IV S mi4 PWM drive signal mi4 Low level; like Phase voltage modulation wave Less than triangular carrier Z m When the comparator outputs a low level, the result is obtained. SiC-Mos Pipe I S mi1 PWM drive signal mi1 and SiC-Mos Pipe II S mi2 PWM drive signal mi2 The low level is obtained by negating the low level using NOT. SiC-Mos Pipe III S mi3 PWM drive signal mi3 and SiC-Mos Pipe IV S mi4 PWM drive signal mi4 It is a high level.

7. The energy feedback high power factor air conditioning compressor drive system as described in claim 1, characterized in that, The energy feedback control module includes: Two-phase voltage modulation waveform conversion module II converts the shutdown energy feedback circuit in a rotating coordinate system. d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transformed into a two-phase stationary coordinate system α Axis voltage modulated wave and β Axis voltage modulated wave ; Three-phase voltage modulation wave conversion module II converts the two-phase stationary coordinate system... α Axis voltage modulated wave and β Axis voltage modulated wave Transformed into a three-phase voltage modulation wave in a three-phase stationary coordinate system; Sine modulation module II performs per-unit processing on the three-phase voltage modulation wave to obtain the per-unitized three-phase voltage modulation wave. Based on the per-unitized three-phase voltage modulation wave and the triangular carrier wave... Z g The magnitude comparison generates the drive signal for the combined switching device in the shutdown energy feedback circuit.

8. The energy feedback high power factor air conditioning compressor drive system as described in claim 7, characterized in that, The two-phase voltage modulation wave conversion module II will d Shaft reference voltage setpoint and q Shaft reference voltage setpoint Transform into α Axis voltage modulated wave and β Axis voltage modulated wave The method is as follows: d Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gαp1 , q Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gαp2 intermediate variables v gαp1 Subtract intermediate variables v gαp2 get α Axis voltage modulated wave ,in, θ g The angle corresponding to the rotating coordinate system of the shutdown energy feedback circuit; d Shaft reference voltage setpoint Multiply by sin θ g Obtain intermediate variables v gβp1 , q Shaft reference voltage setpoint cos θ g Obtain intermediate variables v gβp2 intermediate variables v gβp1 Add intermediate variables v gβp2 get β Axis voltage modulated wave .

9. The energy feedback high power factor air conditioning compressor drive system as described in claim 7, characterized in that, The three-phase voltage modulation wave conversion module II will α Axis voltage modulated wave and β Axis voltage modulated wave The method for converting it into a three-phase voltage modulation wave is as follows: a Phase voltage modulation wave equal α Axis voltage modulated wave ; α Axis voltage modulated wave Multiply by 1 / 2 to get the intermediate variable. v tempα2 ; β Axis voltage modulated wave Multiply by 0.866 to obtain the intermediate variable. v tempβ2 ; intermediate variables v tempβ2 Subtract intermediate variables v tempα2 ,get b Phase voltage modulation wave ; intermediate variables v tempα2 Subtract the intermediate variable after taking the negative value v tempβ2 ,get c Phase voltage modulation wave .

10. The energy feedback high power factor air conditioning compressor drive system as described in claim 7, characterized in that, The sinusoidal modulation module II modulates the normalized three-phase voltage modulation wave with a triangular carrier wave. Z g The method for generating the drive signal for the combined switching device in the shutdown energy feedback circuit by comparing the magnitudes is as follows: The normalized parts are compared using a comparator. Phase voltage modulation wave With triangular carrier Z g Size; like Phase voltage modulation wave Greater than or equal to triangular carrier Z g When the comparator outputs a high level, the result is obtained. SiC-Mos Pipe I S gi1 PWM drive signal gi1 and SiC-Mos Pipe II S gi2 PWM drive signal gi2 The high level is obtained by negating the high level using NOT. SiC-Mos Pipe III S gi3 PWM drive signal gi3 and SiC-Mos Pipe IV S gi4 PWM drive signal gi4 Low level; like Phase voltage modulation wave Less than triangular carrier Z g When the comparator outputs a low level, the result is obtained. SiC-Mos Pipe I S gi1 PWM drive signal gi1 and SiC-Mos Pipe II S gi2 PWM drive signal gi2 The low level is obtained by negating the low level using NOT. SiC-Mos Pipe III S gi3 PWM drive signal gi3 and SiC-Mos Pipe IV S gi4 PWM drive signal gi4 It is a high level.

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