Wide-angle scanning ultra-wideband dual-polarized phased array antenna

Abstract

A wide-angle scanning ultra-wideband dual-polarized phased array antenna includes a radiating element layer, a wide-angle matching layer disposed above the radiating element layer, a balanced feeding structure, and a metal ground plane. The radiating element layer includes a horizontal dielectric substrate, dipole elements periodically arranged in a rectangular grid on one surface of the horizontal dielectric substrate, and reinforcing coupling patches periodically arranged on the other surface of the horizontal dielectric substrate. Each dipole element includes two spaced radiating arms, one of which has a via. The balanced feeding structure includes parallel grounding twin lines, a feed line, and open-circuit stubs, each corresponding to a dipole element. One end of each of the two parallel grounding twin lines is connected to the metal ground plane, and the other end is connected to different radiating arms of the dipole element. One end of the feed line is connected to a coaxial line, and the other end extends through the via to connect with the open-circuit stub. The open-circuit stub is located above both radiating arms of the dipole element. The balanced feeding structure provides higher degrees of freedom and a wider bandwidth.

Description

Technical Field

[0001] This invention relates to the field of phased array antenna technology, and specifically to a wide-angle scanning ultra-wideband dual-polarized phased array antenna. Background Technology

[0002] With the development of modern electronic science and technology, the integration requirements for electronic devices are increasing. To cope with the increasingly complex modern warfare environment, multi-functional combat platforms have become a crucial development trend. Taking the navy as an example, future warships will be integrated combat platforms combining multiple subsystems such as communication, radar, electronic warfare, and positioning systems. Different radio frequency systems operate in different frequency bands; for example, there are C-band weather radars, and guidance and detection radars operating in the X-band and Ku-band respectively. In fact, the antenna feed system is often the largest and heaviest component in radar and electronic jamming systems. If these individual narrowband antennas or arrays of different frequency bands were sequentially loaded onto the equipment platform, it would not only occupy a large amount of the platform's limited usable area, increasing installation and maintenance costs, but also result in an excessively high radar cross-section. Therefore, designing ultra-wideband phased array antennas that can cover multiple frequency bands can not only meet the needs of shared transmission and reception across different frequency bands and achieve multi-functional common aperture, but also save on manufacturing costs and reduce the difficulty of installation and maintenance.

[0003] Traditional broadband phased array antenna design methods struggle to simultaneously achieve broadband and ultra-wide-angle scanning. For example, research has shown that broadband dual-polarized phased array antennas using Archimedean spiral antennas as the array can achieve a maximum grating-lobe-free scanning angle of 30° in the 0.94-2.1 GHz band by adopting an aperiodic concentric ring arrangement and optimizing with a genetic algorithm; microstrip patch phased arrays can achieve a maximum scanning angle of 66°, but the bandwidth is only 3.3%. Vivaldi antennas are a general term for a type of aperiodic continuously tapered short-fire antenna, including slotted antennas, tapered slotted antennas, and end-fire slotted line antennas. Their approach to extending bandwidth is to lower the minimum cutoff frequency by longitudinally extending the element size. Therefore, to achieve ultra-wideband performance, the height of a Vivaldi antenna is typically 2-3λ. high Such a high profile limits their use on carrier platforms with high aerodynamic requirements. Furthermore, the large longitudinal current in their slot lines leads to an increase in cross-polarization components during antenna scanning. Especially during diagonal scanning, the cross-polarization components are often observed to be even greater than the main polarization components. In 2003, Munk collaborated with Harris Corporation to develop a 28×28 dual-polarization array prototype operating at 2-18 GHz. The structural profile of this prototype above the floor was only λ. low / 10(λ low(This is the lowest operating frequency). Later, this type of antenna was generally referred to as a tightly coupled phased array antenna. In the aforementioned tightly coupled antenna prototype, an external balun, a biaxial shaft, and a grounded shielding device were used as the feed network. However, this external feed structure suffered from high cost and large size and weight, making it difficult to implement in practical applications.

[0004] To address this issue, Vouvakis's team proposed a planar ultra-wideband modular antenna (PUMA) in 2010. This design features a very simple feeding structure: the dipole is fed by only a parallel double-wire system, consisting of a ground wire and a signal wire connected to the inner conductor of a coaxial connector. Because the current on the signal wire is greater than the current on the ground wire, the array generates a periodic net current along its longitudinal axis. A short-circuit probe is needed to shift this common-mode resonance out of the operating frequency band. Ultimately, this antenna array operates in the 7–21 GHz frequency band, achieving ±45° scanning angle coverage. However, due to the unbalanced feeding, the operating bandwidth is relatively narrow, only three octaves.

[0005] In summary, traditional ultra-wideband antennas suffer from narrow scanning, high profile, and poor polarization purity. While the dipole-based parallel dual-line feeding method proposed by the Vouvakis team can achieve ultra-wideband scanning with a lower profile, its direct use of unbalanced feeding in the feeding network design leads to drawbacks such as narrow operating bandwidth and potential additional radiation and losses from surface currents in the outer conductor, resulting in pattern distortion. Therefore, there is still room for improvement in the design of ultra-wideband antenna arrays. Summary of the Invention

[0006] The purpose of this invention is to overcome the shortcomings of the prior art and provide a wide-angle scanning ultra-wideband dual-polarized phased array antenna with higher degrees of freedom and wider bandwidth based on a balanced feeding structure.

[0007] To achieve the above objectives, the technical solution of the present invention is implemented as follows:

[0008] This invention provides a wide-angle scanning ultra-wideband dual-polarized phased array antenna, comprising a radiating element layer, a wide-angle matching layer disposed above the radiating element layer, a balanced feed structure disposed in conjunction with the radiating element layer, and a metal ground plane disposed below the balanced feed structure. The radiating element layer includes a horizontal dielectric substrate, dipole sub-elements arranged in a rectangular grid periodically on one surface of the horizontal dielectric substrate, and reinforcing coupling patches periodically arranged on the other surface of the horizontal dielectric substrate. The reinforcing coupling patches are perpendicularly aligned with the vertical intersections of four adjacent dipole sub-elements. Each of the dipole units includes two spaced-apart radiating arms, and one of the radiating arms is provided with a via. The balanced feed structure includes parallel grounding twins, a feed line, and an open-circuit stub, which correspond one-to-one with the dipole units. One end of the two parallel grounding twins is connected to the metal grounding plate, and the other end is respectively connected to different radiating arms of the dipole unit. One end of the feed line is connected to a coaxial line, and the other end extends through the via into the wide-angle matching layer and connects to the open-circuit stub. The open-circuit stub is located above both radiating arms of the dipole unit.

[0009] Unlike the unbalanced feeding method proposed by the Vouvakis team, which uses parallel double-wire feeds for dipoles, this invention's wide-angle scanning ultra-wideband dual-polarized phased array antenna, based on the principle of balanced and unbalanced conversion of baluns, employs a balanced feeding structure with two parallel ground wires. The two parallel ground wires form two grounding points. The feed wires do not directly connect to the radiating arms of the dipole element; instead, they pass through a via on one of the radiating arms and connect to an open stub, ensuring that the currents on the two radiating arms of the dipole element are of equal amplitude and opposite direction. This directly removes the common-mode resonant point outside the operating frequency band without requiring a short circuit. Furthermore, traditional unbalanced feeding structures can only adjust the radiation frequency band by adjusting the spacing and thickness of the parallel double wires, resulting in low freedom. In contrast, this invention allows for adjustment of the radiation frequency band by adjusting parameters such as the spacing and thickness of the parallel ground wires, the thickness of the feed wires, and the shape and size of the open stub, providing greater freedom and achieving a wider bandwidth.

[0010] In one embodiment, the wide-angle matching layer includes a metasurface dielectric substrate and metal patches arranged periodically on the surface of the metasurface dielectric substrate, the metal patches being designed to be subwavelength in size and having through slots on their surfaces.

[0011] In one embodiment, the metal patch is circular in shape and divided into four right-angled sector patches by a central cross groove.

[0012] In one embodiment, the wide-angle matching layer further includes a dielectric matching substrate disposed between the metasurface dielectric substrate and the dipole unit, the open-circuit stub is printed on the side of the dielectric matching substrate facing the metasurface dielectric substrate, and the feed line extends through the via into the dielectric matching substrate and is connected to the open-circuit stub.

[0013] In one embodiment, the open branch is designed as a metal patch consisting of a circle, a strip, and a trapezoid connected in sequence, and the trapezoidal and circular portions of the open branch are located above different radial arms.

[0014] In one embodiment, a supporting dielectric plate is provided between the radiating unit layer and the metal ground plane. Through-holes are formed on the horizontal dielectric substrate and the supporting dielectric plate corresponding to the grid blanks of the dipole unit arrangement. A blind via is recessed on the side of the wide-angle matching layer facing the radiating unit layer corresponding to the through-holes. Through-holes are correspondingly provided on each substrate used to support the balanced feed structure. By drilling holes in the substrates, air columns are introduced to reduce the dielectric constant, thereby eliminating surface waves that may occur in the array within the operating frequency band.

[0015] In one embodiment, the dipole unit consists of two rhomboid metal sheets of the same shape and size spaced apart, the two rhomboid metal sheets being symmetrically distributed based on the intermediate gap.

[0016] In one embodiment, the dielectric support plate is composed of several layers of Rogers dielectric plates.

[0017] In one embodiment, the feed line is connected to the coaxial line via a via in the metal ground plane.

[0018] In one embodiment, the wide-angle matching layer includes a first dielectric substrate, a second dielectric substrate, and a third dielectric substrate stacked sequentially. The first dielectric substrate, the second dielectric substrate, and the third dielectric substrate have through holes of the same position and the same diameter at the grid blank spaces corresponding to the arrangement of the dipole units.

[0019] Compared with existing technologies, the wide-angle scanning ultra-wideband dual-polarized phased array antenna provided by this invention has the following advantages: Based on the balun principle, a balanced structure such as parallel grounded dual lines is designed to feed the dipole element, thereby removing the common-mode resonant point outside the operating frequency band and avoiding imbalance on the two radiating arms of the dipole element. Short-circuit lines are not required. Simultaneously, impedance matching is effectively adjusted through open-circuit stubs connected to the feed lines, further expanding the bandwidth. Furthermore, the array profile height is only 0.39 times the high-frequency wavelength, significantly lower than that of traditional Vivaldi antennas, effectively reducing cross-polarization. The resulting tightly coupled antenna array impedance bandwidth is 9.2-45 GHz (Active S-band when firing side-firing).11 <-8.6, E-plane 45° scan Active S 11 <-8.6, H-plane 45° scan Active S 11 <-7), reaching 4.8 octaves; simple structure, small size, light weight, easy to process and assemble, low cost, and strong engineering practicality.

[0020] Other advantages of the present invention will be described in detail in the following detailed description section with reference to the accompanying drawings. Attached Figure Description

[0021] The accompanying drawings, which form part of this invention, are used to provide a further understanding of the invention. The illustrative embodiments of the invention and their descriptions are used to explain the invention and do not constitute an improper limitation of the invention.

[0022] In the attached diagram:

[0023] Figure 1 This is a perspective view of an embodiment of a wide-angle scanning ultra-wideband dual-polarized phased array antenna according to the present invention; the antenna array shown in the figure is a 10×10 array, but only the central 8×8 antenna array element is fed, and the outer ring of antenna array elements are dummy elements.

[0024] Figure 2 for Figure 1 A top view of the metasurface structure corresponding to one antenna element in the embodiment shown.

[0025] Figure 3 for Figure 1 The illustrated embodiment shows a partial top view of the radiating unit layer after the wide-angle matching layer has been removed;

[0026] Figure 4 for Figure 1 A schematic diagram of the dipole unit and balanced feed structure at the first angle in the embodiment shown;

[0027] Figure 5 for Figure 1 A schematic diagram of the dipole unit and balanced feed structure at the second angle in the embodiment shown;

[0028] Figure 6 for Figure 1 A schematic diagram of the main parameters of the embodiment shown;

[0029] Figure 7 for Figure 1 The illustrated embodiment is shown as a side view after perspective processing;

[0030] Figure 8 for Figure 1 The active reflection coefficient of the antenna array element scanning in the E-plane in the embodiment shown;

[0031] Figure 9 for Figure 1 The active reflection coefficient of the antenna array element scanning in the H-plane in the embodiment shown;

[0032] Figure 10 for Figure 1 The isolation of the antenna array elements scanning in the E-plane in the embodiment shown;

[0033] Figure 11 for Figure 1 The isolation of the antenna array elements scanning in the H-plane in the embodiment shown;

[0034] Figure 12 for Figure 1 The gain of the antenna array element in the illustrated embodiment when it is not scanning in an infinitely large array environment;

[0035] Figure 13 (a) shows the E-plane radiation pattern of the antenna array element at 10 GHz, and (b) shows the H-plane radiation pattern of the antenna array element at 10 GHz.

[0036] Figure 14 (a) shows the E-plane radiation pattern of the antenna array element at 20 GHz, and (b) shows the H-plane radiation pattern of the antenna array element at 20 GHz.

[0037] Figure 15 (a) shows the E-plane radiation pattern of the antenna array element at 30 GHz, and (b) shows the H-plane radiation pattern of the antenna array element at 30 GHz.

[0038] Figure 16 (a) shows the E-plane radiation pattern of the antenna array element at 40 GHz, and (b) shows the H-plane radiation pattern of the antenna array element at 40 GHz.

[0039] Explanation of reference numerals in the attached figures: 1 Radiation unit layer, 11 Dipole unit, 113 Radiation arm, 12 Horizontal dielectric substrate, 13 Via, 14 Reinforcing coupling patch, 2 Wide-angle matching layer, 21 Metal patch, 22 Metasurface dielectric substrate, 23 Dielectric matching substrate, 3 Balanced feed structure, 30 Parallel grounding twin wires, 301 Parallel grounding wire, 302 Parallel grounding wire, 31 Open stub, 32 Supporting dielectric board, 33 Feed line, 4 Metal ground plane, 5 Through hole. Detailed Implementation

[0040] To further explain the technical solution of the present invention, the present invention will be described in detail below with reference to the accompanying drawings, in which the same reference numerals denote the same parts.

[0041] like Figure 1As shown, this embodiment is a wide-angle scanning ultra-wideband dual-polarized phased array antenna. In this embodiment, the dual-polarized phased array antenna arranges 100 antenna elements in a 10×10 two-dimensional arrangement, only feeding the central 8×8 antenna elements, and connecting the surrounding antenna elements to a 50-ohm matching load as dummy elements. This array is only one specific implementation of the wide-angle scanning ultra-wideband dual-polarized phased array antenna. According to actual application requirements, the infinite array environment can be extended to any practical finite array environment.

[0042] See also Figure 1-7 The wide-angle scanning ultra-wideband dual-polarized phased array antenna of this embodiment includes a radiating element layer 1, a wide-angle matching layer 2 disposed above the radiating element layer 1, a balanced feed structure 3 disposed in conjunction with the radiating element layer 1, and a metal ground plane 4 disposed below the balanced feed structure 3. The radiating element layer 1 includes a horizontal dielectric substrate 12, dipole sub-elements 11 periodically arranged in a rectangular grid on one surface of the horizontal dielectric substrate 12, and reinforcing coupling patches 14 periodically arranged on the other surface of the horizontal dielectric substrate 12. The reinforcing coupling patches 14 are reinforcing coupling circular metal patches, located below the horizontal dielectric substrate 12 and directly opposite the vertical intersections of the four adjacent dipole sub-elements 11. Each dipole sub-element 11 includes two spaced radiating arms 113, and one of the radiating arms 113 is provided with a via 13. The balanced feed structure 3 includes parallel grounded double lines 30, a feed line 33, and an open-circuit stub 31. The balanced feed structure 3 corresponds one-to-one with the dipole sub-elements 11. Figure 4 As shown, the balanced feed structure 3 is a vertically arranged double parallel grounding wire balanced feed structure. One end of the two parallel grounding wires (i.e., parallel grounding wire 301 and parallel grounding wire 302) of the parallel grounding double wire 30 is connected to the metal grounding plate 4, and the other end is connected to different radiating arms 113 of the same dipole unit 11. The metal grounding plate 4 has a hole cut in the grounding plate between the 50-ohm coaxial line and the feeder 33. One end of the feeder 33 is directly connected to the inner core of the coaxial line through a via on the metal grounding plate 4, without requiring other structures to achieve impedance gradient. The other end of the feeder 33 extends through the via 13 on the radiating arm 113 to connect with the open-circuit stub 31, which adjusts the reactance of the feeder 33. The open-circuit stub 31 spans the gap between the two radiating arms 113 of the dipole unit 11 and is located above the two radiating arms 113 of the dipole unit 11 to introduce a phase difference.

[0043] Specifically, the wide-angle matching layer 2 includes a metasurface dielectric substrate 22, metal patches 21 periodically arranged on the surface of the metasurface dielectric substrate 22, and a dielectric matching substrate 23 disposed between the metasurface dielectric substrate 22 and the dipole unit 11. The metasurface dielectric substrate 22 and the metal patches 21 periodically arranged on the surface of the metasurface dielectric substrate 22 together constitute the metasurface material matching layer. The metal patches 21 are composed of circular metal patches with subwavelength dimensions and central cross-shaped slots, which can increase the degree of freedom of circuit tuning and improve the VSWR of the array scanning in the H-plane. Open-circuit stubs 31 are printed on the side of the dielectric matching substrate 23 facing the metasurface dielectric substrate 22. Feed lines 33 extend through vias 13 into the dielectric matching substrate 23 and connect to the open-circuit stubs 31 printed on the surface of the dielectric matching substrate 23. Based on this, the structure of any antenna array element includes a horizontally arranged dipole element 11 and a horizontal dielectric substrate, a wide-angle matching layer above the dipole element 11, a vertically arranged balanced feed structure 3 passing through the dipole element 11, and a metal ground plane 4 below the balanced feed structure 3.

[0044] In other embodiments, the wide-angle matching layer may also be composed of a first dielectric substrate, a second dielectric substrate, and a third dielectric substrate stacked in sequence. The first dielectric substrate, the second dielectric substrate, and the third dielectric substrate are pure dielectric substrates. Through holes with the same position and diameter are opened in the grid blank spaces corresponding to the dipole units on the first dielectric substrate, the second dielectric substrate, and the third dielectric substrate.

[0045] like Figure 3 As shown, in this embodiment, the open stub 31 is designed as a metal patch consisting of a circle, a strip, and a trapezoid connected in sequence, and the trapezoidal part and the circle part of the open stub 31 are located above different radiating arms 113, so as to better adjust the reactance of the feeder 33.

[0046] See also Figure 3 and Figure 7 In this embodiment, a supporting dielectric plate 32 is provided between the radiating unit layer 1 and the metal ground plane 4. The supporting dielectric plate 32 is a supporting structure composed of several layers of Rogers 5880 dielectric plates, which supports the parallel grounding twin lines 30 and the feed line 33. Through holes 5 are opened on the horizontal dielectric substrate 12 and the supporting dielectric plate 32 at the grid blank spaces corresponding to the dipole units 11. Through holes of the same diameter are opened on the side of the dielectric matching substrate 23 facing the radiating unit layer 1 corresponding to the through holes 5. That is, except for the metasurface dielectric substrate 22, the dielectric matching substrate 23, the horizontal dielectric substrate 12 and the supporting dielectric plate 32 are all perforated. Air columns are introduced by perforation to reduce the dielectric constant, thereby eliminating surface waves that may occur in the array within the operating frequency band and reducing the overall mass of the array.

[0047] Figure 6The specific dimensions of the dipole unit 11 and the open-circuit stub 31 are shown, in conjunction with... Figure 6 The radius of the through hole 5 on the support medium plate 32 of the dimensions shown is 1.25 mm. Figure 13-16 The radiation pattern of this embodiment when implementing dual-polarization scanning is given. It can be seen that this embodiment achieves an impedance bandwidth of 9.2–45 GHz and an active reflection coefficient of Active S during side-firing. 11 ≤-8.6. Elevation plane scanning angle E-plane ±45°, Active reflectance coefficient. 11 ≤-8.6, H-plane ±45°, Active reflectance S 11 ≤-7.

[0048] Figure 8 The figure shows the active VSWR of the infinite array scanned in the E-plane in this embodiment. As can be seen from the figure, this embodiment can achieve an active reflection coefficient of less than -8.6 in the frequency band of 9.2-45 GHz when the scanning angle is 0°. When the scanning angle is 45°, the active reflection coefficient is less than -9 in the same frequency band.

[0049] Figure 9 The figure shows the active VSWR of the infinite array scanning in the H-plane in this embodiment. As can be seen from the figure, when the scanning angle is 0°, this embodiment can achieve an active reflection coefficient of less than -8.6 in the frequency band of 9.2-45GHz. When scanning to 45°, it can achieve an active reflection coefficient of less than -7 in the same frequency band.

[0050] Figure 8 and Figure 9 In the test, no spikes were observed in the active reflection coefficients, indicating that no common-mode resonant points were found. This also reflects that the balanced feed structure removed the common-mode resonant points from the operating frequency band.

[0051] Figure 10 This figure shows the isolation of the infinite array scanning in the E-plane in this embodiment. As can be seen from the figure, this embodiment can achieve an isolation of less than -12dB in the frequency band of 9.2 to 45 GHz, except for the low frequency range, when the scanning angle is 0°. When the scanning angle is 45°, the isolation of less than -12dB can be achieved in the same frequency band.

[0052] Figure 11 This figure shows the isolation of the infinite array scanning in the H-plane in this embodiment. As can be seen from the figure, this embodiment can achieve an isolation of less than -12dB in the frequency band of 9.2-45GHz, except for the low frequency range, when the scanning angle is 0°. When the scanning angle is 45°, the isolation of less than -12dB can be achieved in the same frequency band.

[0053] Figure 12This represents the gain of coplanar polarization of the infinite array cells in this embodiment under non-scanning conditions.

[0054] Figure 13 for Figure 2 The radiation patterns of the E-plane and H-plane of the main polarization surface of the array element in the non-scanning state at 10 GHz are shown. (a) is the radiation pattern of the E-plane in the side-firing state at 10 GHz in this embodiment; (b) is the radiation pattern of the H-plane in the side-firing state at 10 GHz in this embodiment.

[0055] Figure 14 for Figure 2 The radiation patterns of the E-plane and H-plane of the main polarization surface of the array element in the non-scanning state at 20 GHz are shown. (a) is the radiation pattern of the E-plane in the side-firing state at 20 GHz in this embodiment; (b) is the radiation pattern of the H-plane in the side-firing state at 20 GHz in this embodiment.

[0056] Figure 15 for Figure 2 The radiation patterns of the E-plane and H-plane of the main polarization surface of the array element in the non-scanning state at 30 GHz are shown. (a) is the radiation pattern of the E-plane in the side-firing state at 30 GHz in this embodiment; (b) is the radiation pattern of the H-plane in the side-firing state at 30 GHz in this embodiment.

[0057] Figure 16 for Figure 2 The radiation patterns of the E-plane and H-plane of the main polarization surface of the array element in the non-scanning state at 40 GHz are shown; (a) is the radiation pattern of the E-plane in the side-firing state at 40 GHz in this embodiment; (b) is the radiation pattern of the H-plane in the side-firing state at 40 GHz in this embodiment.

[0058] This embodiment of the wide-angle scanning ultra-wideband dual-polarized phased array antenna, based on the balun principle, designs a parallel-grounded dual-line feed for the dipole element, thereby removing the common-mode resonant point outside the operating frequency band and avoiding imbalance on the two radiating arms of the dipole element. It eliminates the need for short-circuit lines. Simultaneously, the open-circuit stubs connected to the feed lines effectively adjust impedance matching, further extending the bandwidth. Furthermore, the array profile height is only 0.39 times the high-frequency wavelength, significantly lower than traditional Vivaldi antennas, effectively reducing cross-polarization. The resulting tightly coupled antenna array has an impedance bandwidth of 9.2-45 GHz (Active Segmentation when firing side-firing). 11 <-8.6, E-plane 45° scan Active S 11 <-8.6, H-plane 45° scan Active S 11 <-7), reaching 4.8 octaves; simple structure, small size, light weight, easy to process and assemble, low cost, and strong engineering practicality.

[0059] The above description is merely a specific embodiment of the present invention. It should be noted that any variations or substitutions that can be easily conceived by those skilled in the art within the technical scope disclosed in the present invention should be included within the protection scope of the present invention.

Claims

1. A wide-angle scanning ultra-wideband dual-polarized phased array antenna, characterized in that, The system includes a radiating unit layer (1), a wide-angle matching layer (2) disposed above the radiating unit layer (1), a balanced feeding structure (3) configured in conjunction with the radiating unit layer (1), and a metal ground plane (4) disposed below the balanced feeding structure (3). The radiating unit layer (1) includes a horizontal dielectric substrate (12), dipole sub-units (11) arranged in a rectangular grid on one surface of the horizontal dielectric substrate (12), and reinforcing coupling patches (14) arranged in a periodic manner on the other surface of the horizontal dielectric substrate (12). The reinforcing coupling patches (14) are perpendicular to the vertical intersections of the four adjacent dipole sub-units (11). Each dipole sub-unit (11) includes two spaced and symmetrical radiating arms (11). 3) One of the radiating arms (113) is provided with a via (13). The balanced power supply structure (3) includes a parallel grounding double line (30), a feed line (33), and an open stub (31) that correspond one-to-one with the dipole unit (11). One end of the two parallel grounding lines of the parallel grounding double line (30) is connected to the metal grounding plate (4), and the other end is connected to different radiating arms (113) of the dipole unit (11). One end of the feed line (33) is connected to the coaxial line, and the other end extends through the via (13) into the wide-angle matching layer (2) and is connected to the open stub (31). The open stub (31) is located above the two radiating arms (113) of the dipole unit (11).

2. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in claim 1, characterized in that, The wide-angle matching layer (2) includes a metasurface dielectric substrate (22) and metal patches (21) arranged periodically on the surface of the metasurface dielectric substrate (22). The metal patches (21) are designed to be subwavelength and have through slots on their surface.

3. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in claim 2, characterized in that, The metal patch (21) is circular in shape and divided into four right-angled sector patches by a cross-shaped groove in the middle.

4. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in claim 2, characterized in that, The wide-angle matching layer (2) also includes a dielectric matching substrate (23) disposed between the metasurface dielectric substrate (22) and the dipole unit (11). The open-circuit stub (31) is printed on the side of the dielectric matching substrate (23) facing the metasurface dielectric substrate (22). The feed line (33) extends through the via (13) into the dielectric matching substrate (23) and is connected to the open-circuit stub (31).

5. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in any one of claims 1-4, characterized in that, The open branch (31) is designed as a metal patch consisting of a circle, a strip, and a trapezoid connected in sequence, and the trapezoidal part and the circle part of the open branch (31) are located above different radial arms (113).

6. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in any one of claims 1-4, characterized in that, A supporting dielectric plate (32) is provided between the radiating unit layer (1) and the metal ground plane (4). Through holes (5) are provided on the horizontal dielectric substrate (12) and the supporting dielectric plate (32) at the grid blank spaces corresponding to the arrangement of the dipole units (11). A blind hole is recessed on the side of the wide-angle matching layer (2) facing the radiating unit layer (1) corresponding to the through hole (5).

7. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in any one of claims 1-4, characterized in that, The dipole unit (11) consists of two rhomboid metal sheets of the same shape and size, spaced apart, with the two rhomboid metal sheets symmetrically distributed based on the middle gap.

8. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in claim 6, characterized in that, The supporting medium plate (32) is composed of several layers of Rogers5880 medium plates.

9. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in any one of claims 1-4, characterized in that, The feed line (33) is connected to the coaxial line through a via on the metal ground plane (4).

10. The wide-angle scanning ultra-wideband dual-polarized phased array antenna as described in claim 1, characterized in that, The wide-angle matching layer (2) includes a first dielectric plate, a second dielectric plate and a third dielectric plate stacked in sequence. The first dielectric plate, the second dielectric plate and the third dielectric plate have through holes with the same position and the same diameter in the grid blank space corresponding to the dipole unit (11).

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