A phased array antenna for simultaneous reception at different frequencies

Abstract

The embodiment of the present application provides a phased array antenna for simultaneous reception at different frequencies, which relates to the technical field of phased array antennas. The antenna includes: N first-level power division networks, each of which is connected to M antenna unit links, and the number of network channels of the first-level power division network is M, where M is a positive integer; O second-level power division networks, each of which is connected to N first-level power division networks, and the number of network channels of the second-level power division network is N, where N is a positive integer; two third-level power division networks, each of which is connected to 2O second-level power division networks, and the number of network channels of the third-level power division network is 2O, where O is a positive integer. The technical solution of the present application solves the problems of a large number of components, difficulty in integration, high cost, and high control complexity of high-frequency dual-beam satellite communication phased array antennas, and the overall structure of the antenna is simple.

Description

Technical Field

[0001] The present application relates to the technical field of phased array antennas, and in particular to a phased array antenna for simultaneous reception at different frequencies. Background Art

[0002] At present, there are two solutions for satellite communication phased array antennas to achieve dual-beam simultaneous reception. One is to directly adopt the dual-beam phased array antenna architecture, that is, to design two completely independent RF links, each of which has its own independent low-noise amplifier chip (referred to as LNA), digitally controlled phase shifter chip (referred to as phase shifter), digitally controlled attenuator chip (referred to as attenuator), power divider, etc. The two beams are completely transmitted from two separate RF links, such as dual-beam satellite communication phased array antennas. Another solution is to design a broadband phased array antenna, which has only one set of RF links with integrated delay chips. The delay chip compensates for the aperture transition time introduced by the phased array antenna scanning, thereby having a wider working instantaneous bandwidth. The broadband phased array antenna with integrated delay chips can theoretically receive incoming waves of any frequency and expected angle within the working bandwidth, thus having the ability to receive dual beams simultaneously, such as broadband delay satellite communication phased array antennas.

[0003] However, the solution using a dual-beam phased array antenna architecture (dual-beam satellite communication phased array antenna) has problems with increased device cost, increased device density, and increased size, while the solution of designing a broadband phased array antenna (broadband delayed satellite communication phased array antenna) requires loading a delay line chip or an equalizer chip, which makes the phased array antenna have problems such as complex design, high cost, high control complexity, and limited performance. Summary of the invention

[0004] The embodiments of the present application provide a phased array antenna for simultaneous reception at different frequencies to solve the problems of complex design, high cost, high control complexity, and limited performance of large-aperture broadband delayed satellite communication phased array antennas.

[0005] Other features and advantages of the present application will become apparent from the following detailed description, or may be learned in part by the practice of the present application.

[0006] According to a first aspect of an embodiment of the present application, there is provided a phased array antenna for simultaneous reception at different frequencies, comprising:

[0007] N first-level power division networks, each of which is connected to M antenna unit links, and the number of network channels of the first-level power division network is M, where M is a positive integer;

[0008] O second-level power division networks, each of which is connected to N first-level power division networks, and the number of network channels of the second-level power division network is N, where N is a positive integer;

[0009] Two third-level power division networks, each of which is connected to 2O second-level power division networks, and the number of network channels of the third-level power division network is 2O, where O is a positive integer;

[0010] Each second-level power division network and the N first-level power division networks connected to each second-level power division network constitute a standard subarray, and the standard subarray outputs a radio frequency signal and transmits it to two third-level power division networks respectively.

[0011] In some embodiments of the present application, based on the aforementioned solution, the antenna unit link includes: a signal processing unit and an antenna unit connected in sequence.

[0012] In some embodiments of the present application, based on the aforementioned solution, the signal processing unit includes: a low noise amplifier, a digitally controlled phase shifter and a digitally controlled attenuator connected in sequence.

[0013] In some embodiments of the present application, based on the aforementioned solution, the signal processing unit includes: a low noise amplifier and a digitally controlled phase shifter connected in sequence.

[0014] In some embodiments of the present application, based on the aforementioned solution, a 1-to-2 power splitter is provided between each second-level power splitting network and the third-level power splitting network.

[0015] In some embodiments of the present application, based on the above-mentioned solution, a common-end digitally controlled phase shifter is provided on each third-level power division network.

[0016] In some embodiments of the present application, based on the aforementioned scheme, the value of M is 8.

[0017] In some embodiments of the present application, based on the aforementioned scheme, the value of N is 8.

[0018] In some embodiments of the present application, based on the aforementioned scheme, the value of O is 8.

[0019] The technical solution of the present application solves the problems of a large number of high-frequency dual-beam satellite communication phased array antenna components, difficulty in integration, high cost, high control complexity, etc., and the overall structure of the antenna is simple.

[0020] It should be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the present application. BRIEF DESCRIPTION OF THE DRAWINGS

[0021] The drawings herein are incorporated into the specification and constitute a part of the specification, showing embodiments consistent with the present application, and together with the specification, are used to explain the principles of the present application. Obviously, the drawings described below are only some embodiments of the present application, and for ordinary technicians in this field, other drawings can be obtained based on these drawings without creative work. In the drawings:

[0022] Figure 1 A schematic diagram of a link architecture of a phased array antenna for simultaneous reception at different frequencies according to an embodiment of the present application is shown;

[0023] Figure 2 A schematic diagram of a link architecture of a standard sub-array according to an embodiment of the present application is shown;

[0024] Figure 3 A schematic diagram of a link architecture of a phased array antenna for simultaneous reception at different frequencies according to a specific example of the present application is shown;

[0025] Figure 4 A schematic diagram of a link architecture of a standard sub-array according to a specific example of the present application is shown;

[0026] Figure 5 A schematic diagram of sub-array distribution according to a specific example of the present application is shown;

[0027] Figure 6 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=60deg) is shown when beam 2 does not call the common-end digitally controlled phase shifter for phase compensation according to a specific example of the present application;

[0028] Figure 7 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=0deg) is shown when the common-end digitally controlled phase shifter is called for phase compensation and correction of beam 2 according to a specific example of the present application;

[0029] Figure 8 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=30deg) is shown when the common-end digitally controlled phase shifter is used to perform phase compensation and correction on beam 2 according to a specific example of the present application;

[0030] Fig. 9 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=50deg) is shown when the common-end digitally controlled phase shifter is used to perform phase compensation and correction on beam 2 according to a specific example of the present application;

[0031] Fig.10 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=60deg) is shown when the common-end digitally controlled phase shifter is called for phase compensation and correction of beam 2 according to a specific example of the present application;

[0032] Fig.11 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=60deg) is shown when beam 2 does not call the common-end digitally controlled phase shifter for phase compensation according to a specific example of the present application;

[0033] Fig.12 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=0deg) is shown when the common-end digitally controlled phase shifter is called for phase compensation and correction of beam 2 according to a specific example of the present application;

[0034] Fig.13 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=30deg) is shown when the common-end digitally controlled phase shifter is called for phase compensation and correction of beam 2 according to a specific example of the present application;

[0035] Fig.14 The scanning pattern of beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=50deg) is shown when the common-end digitally controlled phase shifter is called for phase compensation and correction of beam 2 according to a specific example of the present application;

[0036] Fig.15 The scanning directional patterns of beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=60deg) are shown when the common-end digitally controlled phase shifter is called to perform phase compensation and correction on beam 2 according to a specific example of the present application. DETAILED DESCRIPTION

[0037] Example embodiments will now be described more fully with reference to the accompanying drawings. However, example embodiments can be implemented in a variety of forms and should not be construed as limited to the examples set forth herein; rather, these embodiments are provided so that this application will be more comprehensive and complete and fully convey the concept of the example embodiments to those skilled in the art.

[0038] In addition, described feature, structure or characteristic can be combined in one or more embodiments in any suitable manner. In the following description, many specific details are provided to provide a full understanding of the embodiments of the present application. However, those skilled in the art will appreciate that the technical scheme of the present application can be put into practice without one or more of the specific details, or other methods, components, devices, steps, etc. can be adopted. In other cases, known methods, devices, realizations or operations are not shown or described in detail to avoid blurring the various aspects of the application.

[0039] It should be noted that the terms "first", "second", etc. in the specification and claims of the present application and the above-mentioned drawings are used to distinguish similar objects, and are not necessarily used to describe a specific order or sequence. It should be understood that the objects used in this way can be interchanged where appropriate, so that the embodiments of the present application described herein can be implemented in an order other than those shown or described.

[0040] In order to make the purpose, technical solution and advantages of the present invention clearer, the technical solution in the embodiment of the present invention will be clearly and completely described below in conjunction with the drawings in the embodiment of the present invention. Obviously, the described embodiment is only a part of the embodiment of the present invention, not all the embodiments. Based on the embodiment of the present invention, all other embodiments obtained by ordinary technicians in this field without creative work are within the scope of protection of the present invention.

[0041] Some embodiments of the present application will be described in detail below in conjunction with the accompanying drawings. In the absence of conflict, the following embodiments and features in the embodiments may be combined with each other.

[0042] See also Figure 1 , shows a schematic diagram of a link architecture of a phased array antenna for simultaneous reception at different frequencies according to an embodiment of the present application.

[0043] See also Figure 2 , shows a schematic diagram of a link architecture of a standard sub-array according to an embodiment of the present application.

[0044] like Figure 1 and Figure 2 As shown, a phased array antenna for simultaneous reception at different frequencies is shown, comprising:

[0045] N first-level power division networks, each of which is connected to M antenna unit links, and the number of network channels of the first-level power division network is M, where M is a positive integer;

[0046] O second-level power division networks, each of which is connected to N first-level power division networks, and the number of network channels of the second-level power division network is N, where N is a positive integer;

[0047] Two third-level power division networks, each of which is connected to 2O second-level power division networks, and the number of network channels of the third-level power division network is 2O, where O is a positive integer;

[0048] Each second-level power division network and the N first-level power division networks connected to each second-level power division network constitute a standard subarray, and the standard subarray outputs a radio frequency signal and transmits it to two third-level power division networks respectively.

[0049] It should be noted that when the antenna is performing beam reception, the N*M antenna unit links receive electromagnetic signals in space and convert the electromagnetic signals into radio frequency signals. The N*M radio frequency signals are synthesized into one radio frequency signal (that is, one standard subarray generates one radio frequency signal) through the first-level power division network and the second-level power division network in turn, and then the power is divided into two radio frequency signals, and then they enter the two third-level power division networks respectively to generate beam 1 and beam 2 respectively.

[0050] In some feasible embodiments, based on the above-mentioned solution, the antenna unit link includes: a signal processing unit and an antenna unit connected in sequence.

[0051] The signal processing unit comprises: a low noise amplifier, a digitally controlled phase shifter and a digitally controlled attenuator which are connected in sequence.

[0052] It should be noted that, in this embodiment, after the electromagnetic signal collected by the antenna unit in space is converted into a radio frequency signal, it needs to be amplified by a background noise amplifier, phase-shifted by a phase shifter, and amplitude-controlled by an attenuator in sequence.

[0053] In some feasible embodiments, based on the above-mentioned solution, the signal processing unit includes: a low-noise amplifier and a digitally controlled phase shifter connected in sequence.

[0054] It should be noted that, in this embodiment, the RF signal obtained after the conversion only needs to be amplified by a noise floor amplifier and phase-shifted by a phase shifter, and does not need to be amplitude-controlled by an attenuator.

[0055] In the present technical solution, whether to perform attenuator amplitude control processing can be determined based on actual conditions.

[0056] In some feasible embodiments, based on the above solution, a 1-to-2 power splitter is provided between each second-level power splitting network and the third-level power splitting network.

[0057] It can be understood that the radio frequency signal synthesized by each standard sub-array is divided into two radio frequency signals by the 1-to-2 power divider and then input into two third-level power division networks respectively.

[0058] In some feasible embodiments, based on the above solution, a common-end digitally controlled phase shifter is provided on each third-level power division network.

[0059] It should be noted that the generated beam 1 is directly output to the common output port, while the generated beam 2 needs to be phase-shifted by the common digitally controlled phase shifter arranged on the third-level power division network before being output to the common output port.

[0060] A specific example of a phased array antenna for simultaneous reception at different frequencies is provided below.

[0061] In this example, the operating frequency of the heterodyne simultaneous receiving phased array antenna is 17.8 GHz to 21.2 GHz, and its link architecture is shown in FIG3 . In this example, the values ​​of M, N, and O are all 8.

[0062] The antenna includes 1024 antenna units, each of which corresponds to 1 low-noise amplifier, 1 digitally controlled phase shifter, and 1 digitally controlled attenuator. That is, the heterodyne simultaneous receiving phased array antenna includes 1024 low-noise amplifiers, 1024 first-stage digitally controlled phase shifters, and 1024 digitally controlled attenuators. Then, the RF signal is synthesized through a 1-to-64 power division network (composed of a first-stage power division network and a second-stage power division network). The 1-to-64 power division network corresponds to 8×8, a total of 64 antenna units. These 64 antenna units constitute a standard subarray. The antenna distribution is as follows: Figure 4 As shown, the example provides a phased array antenna for simultaneous reception at different frequencies, which is composed of 16 standard sub-arrays. Figure 5 shown.

[0063] In order to achieve dual-beam reception, after each standard subarray synthesizes and outputs one RF signal, it is equally divided into two paths using a 1-to-2 power splitter, one of which enters the beam 1 feed synthesis network (the first third-level power splitter network), and the other enters the beam 2 feed synthesis network (the second third-level power splitter network). The beam 1 feed synthesis network is a 1-to-16 equal power splitter network; the beam 2 feed synthesis network is a 1-to-16 equal power splitter network, and each branch is provided with a common-end digitally controlled phase shifter. When the dual-beam satellite communication phased array antenna receives electromagnetic signals from the external space, the antenna converts the received electromagnetic wave signals into radio frequency signals, which are amplified by a low-noise amplifier, phase-shifted by a phase shifter, and amplitude-controlled by an attenuator. The radio frequency signals are synthesized by a 1-to-64 power divider, and then divided into two radio frequency signals by a 1-to-2 power divider. The two signals then enter the beam 1 and beam 2 feed synthesis networks respectively. Beam 1 is directly output to the common output port of beam 1, and beam 2 is phase-shifted by a common-end digitally controlled phase shifter and synthesized to the common output port of beam 2.

[0064] According to the phased array antenna theory, the 32×32 phased array antenna consists of 1,024 antenna elements in total. The element spacing in the x direction is dx, and the element spacing in the y direction is dy. The position of the antenna element in the m-th row and n-th column is ( , ), where 0 < m ≤ 32 and 0 < n ≤ 32. The operating frequency of beam 1 is f1 (17.8 ≤ f1 ≤ 21.2). When the beam scans to ( , ) in space, the compensation phase of the antenna element in the m-th row and n-th column is:

[0065]

[0066] In the above formula, represents the beam constant corresponding to the frequency f1, represents the calibration compensation phase of beam 1 for the antenna element in the m-th row and n-th column, and c represents the speed of light constant.

[0067] The operating frequency of beam 2 is f2 (17.8 ≤ f2 ≤ 21.2). f2 can be the same as or different from f1. When beam 2 scans to ( , ) in space, the compensation phase of the antenna element in the m-th row and n-th column consists of two parts. The first part is phase-shifted and compensated by the numerically controlled phase shifter shared with beam 1, and the second part is phase-shifted and compensated by the numerically controlled phase shifter at the common end of the subarray. The subarray consists of a standard subarray of 64 elements with 8×8. Then the equivalent center position of beam 2 of the antenna element in the m-th row and n-th column for phase shifting by the numerically controlled phase shifter at the common end is , , and the compensation phase of beam 2 of the antenna element in the m-th row and n-th column is:

[0068] ;

[0069] In the above formula, represents the calibration compensation phase of beam 2 for the antenna element in the m-th row and n-th column, represents the correction phase, which can be calculated by the following formula:

[0070] ;

[0071] Among them, , represents the correction factor. The phase shift value of the numerically controlled phase shifter at the common end of beam 2 of the antenna element in the m-th row and n-th column is . By controlling the numerically controlled phase shifter at the common end for phase shifting, beam 2 can be directed to ( , ).

[0072] To verify the effectiveness of this method, the simulation results of the directional pattern of a phased array antenna with different frequencies and simultaneous reception provided in this example are given below.

[0073] Figure 6 The scanning results of the beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=60deg) patterns are shown in the case where the common end digital phase shifter is not used for phase compensation of beam 2. From the simulation results, it can be seen that without additional phase compensation and correction for beam 2, due to the dispersion problem of the phased array, the pointing angle of beam 2 has an angle deviation of about 6deg, which is close to the 3dB beam width of the antenna (6.8deg), and cannot meet the requirements of conventional antenna systems.

[0074] Using the method of the present invention, the common end digital controlled phase shifter is used to perform phase compensation and correction on beam 2. Figure 7~Figure 10 The scanning results of the radiation patterns of beam 1 and beam 2 (f1=20.4GHz, f2=21.2GHz, theta=0, 30deg, 50deg, 60deg) are given. From the simulation results, the beam pointing of beam 1 and beam 2 is highly overlapped. Although the sidelobe level of beam 2 is deteriorated due to the quantization error introduced by the array-level phase shifter, it can still meet the system requirements.

[0075] Fig.11 The scanning results of the beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=60deg) patterns are shown in the case where the common end digital phase shifter is not used for phase compensation of beam 2. From the simulation results, it can be seen that without additional phase compensation and correction for beam 2, due to the dispersion problem of the phased array, the pointing angle of beam 2 has an angle deviation of about 7deg, which is close to the 3dB beam width of the antenna (7.4deg), and cannot meet the requirements of conventional antenna systems.

[0076] Using the method of the present invention, the common end digital controlled phase shifter is used to perform phase compensation and correction on beam 2. Figure 12~Figure 15 The scanning results of beam 1 and beam 2 (f1=20.4GHz, f2=19.6GHz, theta=0, 30deg, 50deg, 60deg) are given. From the simulation results, the beam pointing of beam 1 and beam 2 is highly overlapped. Although the sidelobe level of beam 2 is deteriorated due to the quantization error introduced by the array-level loading phase shifter, it can still meet the system requirements.

[0077] In summary, the heterodyne simultaneous reception phased array antenna provided by the present invention has the following advantages compared with the existing dual-beam satellite communication phased array antenna:

[0078] (1) The existing dual-beam satellite communication phased array antenna is equipped with two sets of completely independent RF links, which requires two sets of low-noise amplifiers and digitally controlled phase shifters. The device density is high, the power consumption is large, the cost is high, and the number of corresponding low-noise amplifiers and digitally controlled phase shifter control circuits is also large. Taking 1024 array elements as an example, the existing dual-beam satellite communication phased array antenna requires 2048 digitally controlled phase shifters, while the heterodyne simultaneous receiving phased array antenna described in the present invention is only equipped with a set of low-noise amplifiers and digitally controlled phase shifters shared by beam 1 and beam 2 at the input end. The devices used are only half of the existing dual-beam satellite communication phased array antenna. With the addition of a secondary digitally controlled phase shifter, a total of 1040 digitally controlled phase shifters are required, and the corresponding low-noise amplifier and digitally controlled phase shifter control circuits are also significantly reduced. When the antenna operating frequency is high (above Ka and Ka bands), it is difficult to achieve dual-beam function with the traditional brick-type architecture. However, with the dual-beam satellite communication phased array antenna solution described in the present invention, the number of components used is very similar to that used for a single beam. Simple separation components can be used to achieve dual-beam function with the traditional brick-type architecture, thereby reducing the difficulty of implementing the dual-beam system.

[0079] (2) The existing dual-beam satellite communication phased array antenna uses two sets of beam resolution control programs, which are used to control the phase shifters of beam 1 and beam 2 for phase shifting. However, in the phased array antenna with different frequencies and simultaneous reception described in the present invention, the control method of beam 1 is completely consistent with the control method of the existing dual-beam satellite communication phased array antenna. Since the operating frequencies of beam 2 and beam 1 are different, when beam 2 completely uses the angle resolution phase corresponding to beam 1, the beam pointing of beam 2 will deviate due to the dispersion effect. According to the frequency difference between beam 2 and beam 1, the present invention adds a correction factor to the angle resolution phase of beam 2, so that beam 2 directly calls the angle resolution phase of beam 1, and corrects it through the second-level digital phase shifter of the link corresponding to beam 2, so that beam 2 beamforming can be completed without separately resolving beam 2, thereby reducing the difficulty of beam control.

[0080] The heterodyne simultaneous receiving phased array antenna provided by the present invention is different from the existing broadband delayed satellite communication phased array antenna in the following aspects:

[0081] (1) The existing broadband delay satellite communication phased array antenna delay chip has the problem of additional parasitic amplitude modulation and phase modulation in different delay states in the working frequency band. It is usually necessary to perform secondary compensation for the additional amplitude and phase of the delay chip in different delay states. In order to obtain the additional amplitude and additional phase of the delay, it is necessary to perform delay calibration on the satellite communication phased array antenna, which is a time-consuming process. In addition, the delay state additional amplitude and additional phase compensation data are huge. When the array scale is large, it takes up a lot of Flash storage space. The FPGA also needs to occupy a large cache space to load the delay state additional amplitude and additional phase compensation data, and it may even be that the FPGA cache space cannot meet the use. The phased array antenna for simultaneous reception at different frequencies described in the present invention does not need to load the delay chip for compensation, and does not need the corresponding auxiliary circuit design. Only a small number of secondary digital phase shifters can realize the function of simultaneous reception at different frequencies of the existing broadband delay satellite communication phased array antenna, which greatly reduces the difficulty of data processing and reduces the demand for Flash and FPGA resources.

[0082] (2) The existing broadband delay satellite communication phased array antenna has a large delay chip loss. When the array size is too large, the scanning angle is large, and the pointing requirements are high, the delay chip has a large number of bits and a large number of delay chip levels. Usually, the loss of a single delay chip is large (the insertion loss of a three-bit delay chip is about 15dB, and the insertion loss of a four-bit delay chip is about 21dB). When the RF link uses a large number of delay chip levels, in order to ensure the system gain of the satellite communication phased array antenna, it is necessary to add multiple low-noise amplifiers for gain compensation. However, since the low-noise amplifier has an in-band gain fluctuation problem, in order to ensure the in-band gain flatness, it is necessary to add an equalizer chip for balance. This sometimes leads to a complex design of broadband delay satellite communication phased array antennas and extremely high costs. The phased array antenna for simultaneous reception of different frequencies described in the present invention does not need to load a delay chip, which greatly reduces the system complexity and reduces the antenna cost.

[0083] (3) The addition of multiple low-noise amplifier chips and multiple delay chips in the existing broadband delayed satellite communication phased array antenna requires the addition of a large number of control and power supply circuits, which greatly increases power consumption and places higher demands on system power supply. However, the heterodyne simultaneous receiving phased array antenna described in the present invention does not require the loading of delay chips, and compared with the narrowband single-beam phased array antenna, it basically does not increase power consumption, which is beneficial to system energy saving and power consumption control.

[0084] Those skilled in the art will readily appreciate other embodiments of the present application after considering the specification and practicing the embodiments disclosed herein. The present application is intended to cover any variations, uses or adaptations of the present application, which follow the general principles of the present application and include common knowledge or customary techniques in the art that are not disclosed in the present application. It should be understood that the present application is not limited to the precise structures described above and shown in the accompanying drawings, and various modifications and changes can be made without departing from the scope thereof. The scope of the present application is limited only by the appended claims.

Claims

1. A phased array antenna for simultaneous reception at different frequencies, characterized in that: include: N first-level power division networks, each of which is connected to M antenna unit links, and the number of network channels of the first-level power division network is M, where M is a positive integer; O second-level power division networks, each of which is connected to N first-level power division networks, and the number of network channels of the second-level power division network is N, where N is a positive integer; Two third-level power division networks, each of which is connected to 2O second-level power division networks, and the number of network channels of the third-level power division network is 2O, where O is a positive integer; Each second-level power division network and the N first-level power division networks connected to each second-level power division network constitute a standard subarray, and the standard subarray outputs a radio frequency signal and transmits it to two third-level power division networks respectively; The antenna unit link comprises: a signal processing unit and an antenna unit connected in sequence; The signal processing unit comprises: a low noise amplifier, a digitally controlled phase shifter and a digitally controlled attenuator connected in sequence; Alternatively, the signal processing unit includes: a low noise amplifier and a digitally controlled phase shifter connected in sequence.

2. The phased array antenna for simultaneous reception at different frequencies according to claim 1, characterized in that: A 1-to-2 power splitter is arranged between each second-level power splitting network and the third-level power splitting network.

3. The phased array antenna for simultaneous reception at different frequencies according to claim 1, characterized in that: Each third-level power division network is provided with a common-end digitally controlled phase shifter.

4. The phased array antenna for simultaneous reception at different frequencies according to claim 1, characterized in that: The value of M is 8.

5. The phased array antenna for simultaneous reception at different frequencies according to claim 1, characterized in that: The value of N is 8.

6. The phased array antenna for simultaneous reception at different frequencies according to claim 1, characterized in that: The value of O is 8.

Images